AD5415YRUZ [ADI]
Dual 12-Bit, High Bandwidth, Multiplying DAC;
| 型号： | AD5415YRUZ |
| 厂家： | 
ADI |
| 描述： | Dual 12-Bit, High Bandwidth, Multiplying DAC |
| 文件： | 总27页 (文件大小：700K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
Dual 12-Bit, High Bandwidth, Multiplying DAC
with 4-Quadrant Resistors and Serial Interface
Data Sheet
AD5415
FEATURES
GENERAL DESCRIPTION
The AD54151 is a CMOS, 12-bit, dual-channel, current output
10 MHz multiplying bandwidth
On-chip 4-quadrant resistors allow flexible output ranges
INL of 1 LSB
digital-to-analog converter (DAC). This device operates from a
2.5 V to 5.5 V power supply, making it suited to battery-powered
applications and other applications. As a result of being manufac-
tured on a CMOS submicron process, this device offers excellent
4-quadrant multiplication characteristics with large signal
multiplying bandwidths of 10 MHz.
24-lead TSSOP package
2.5 V to 5.5 V supply operation
10 V reference input
50 MHz serial interface
2.47 MSPS update rate
Extended temperature range: −40°C to 125°C
4-quadrant multiplication
Power-on reset
The applied external reference input voltage (VREF) determines
the full-scale output current. An integrated feedback resistor (RFB)
provides temperature tracking and full-scale voltage output when
combined with an external current to voltage precision amplifier.
In addition, this device contains the 4-quadrant resistors necessary
for bipolar operation and other configuration modes.
0.5 µA typical current consumption
Guaranteed monotonic
Daisy-chain mode
Readback function
This DAC uses a double-buffered, 3-wire serial interface that is
compatible with SPI®, QSPI™, MICROWIRE™, and most DSP
interface standards. In addition, a serial data out pin (SDO) allows
daisy-chaining when multiple packages are used. Data readback
allows the user to read the contents of the DAC register via the
SDO pin. On power-up, the internal shift register and latches
are filled with 0s, and the DAC outputs are at zero scale.
APPLICATIONS
Portable battery-powered applications
Waveform generators
Analog processing
Instrumentation applications
Programmable amplifiers and attenuators
Digitally controlled calibration
Programmable filters and oscillators
Composite video
The AD5415 DAC is available in a 24-lead TSSOP package. The
EV-AD5415/49SDZ evaluation board is available for evaluating
DAC performance. For more information, see UG-296, Evaluating
the AD5415 Serial Input, Dual-Channel Current Output DAC.
Ultrasound
Gain, offset, and voltage trimming
FUNCTIONAL BLOCK DIAGRAM
V
R3A
R2_3A
R2A
A R1A
REF
R3
2R
R2
2R
R
2R
R1
2R
FB
AD5415
V
DD
R
A
FB
SYNC
SCLK
SDIN
I
I
1A
2A
OUT
12-BIT
R-2R DAC A
INPUT
REGISTER
DAC
REGISTER
SHIFT
REGISTER
OUT
SDO
LDAC
I
I
1B
2B
OUT
12-BIT
R-2R DAC B
INPUT
REGISTER
DAC
REGISTER
OUT
POWER-ON
RESET
CLR
GND
R
B
FB
R1
2R
R
FB
2R
R3
2R
R2
2R
R3B
R2_3B
R2B
V
B R1B
REF
Figure 1.
1 U.S. Patent Number 5,689,257.
Rev. F
Document Feedback
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responsibility is assumed by Analog Devices for its use, nor for any infringements of patents or other
rightsof third parties that may result fromits use. Specifications subject to change without notice. No
license is granted by implication or otherwise under any patent or patent rights of Analog Devices.
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One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A.
Tel: 781.329.4700 ©2004–2015 Analog Devices, Inc. All rights reserved.
Technical Support
www.analog.com
AD5415
Data Sheet
TABLE OF CONTENTS
Features .............................................................................................. 1
Circuit Operation....................................................................... 15
Single-Supply Applications ....................................................... 16
Adding Gain................................................................................ 17
Divider or Programmable Gain Element................................ 17
Reference Selection .................................................................... 18
Amplifier Selection .................................................................... 18
Serial Interface............................................................................ 20
Microprocessor Interfacing....................................................... 22
PCB Layout and Power Supply Decoupling ........................... 24
Overview of the AD5424 to AD5547 Devices............................ 25
Outline Dimensions....................................................................... 26
Ordering Guide .......................................................................... 26
Applications....................................................................................... 1
General Description......................................................................... 1
Functional Block Diagram .............................................................. 1
Revision History ............................................................................... 2
Specifications..................................................................................... 3
Timing Characteristics ................................................................ 5
Absolute Maximum Ratings............................................................ 7
ESD Caution.................................................................................. 7
Pin Configuration and Function Descriptions............................. 8
Typical Performance Characteristics ............................................. 9
Terminology .................................................................................... 14
General Description....................................................................... 15
DAC Section................................................................................ 15
REVISION HISTORY
12/15—Rev. E to Rev. F
7/05—Rev. 0 to Rev. A
Deleted Positive Output Voltage Section..................................... 17
Changes to Adding Gain Section ................................................. 17
Changes to Reference Selection Section...................................... 18
Changes to ADSP21xx to AD5415 Interface Section,
Changes to Features List...................................................................1
Change to General Description.......................................................1
Changes to Specifications.................................................................3
Changes to Timing Characteristics.................................................5
Change to Figure 8 and Figure 9 .....................................................9
Change to Figure 13 ....................................................................... 10
Change to Figure 27 Through Figure 29 ..................................... 12
Change to Figure 32 ....................................................................... 15
Changes to Table 5 and Table 6 .................................................... 15
Change to Stability Section ........................................................... 16
Changes to Voltage-Switching Mode of Operation Section ..... 16
Change to Figure 35 ....................................................................... 16
Changes to Divider or Programmable Gain Element Section.... 17
Changes to Figure 36 Through Figure 38.................................... 17
Changes to Table 7 Through Table 10 ......................................... 19
Added ADSP-BF5xx-to-AD5415 Interface Section................... 22
Change to 80C51/80L51-to-AD5415 Interface Section............ 23
Change to MC68HC11-to-AD5415 Interface Section .............. 23
Change to Power Supplies for the Evaluation Board Section... 24
Changes to Table 13 ....................................................................... 28
Updated Outline Dimensions....................................................... 29
Changes to Ordering Guide.......................................................... 29
ADSP-BF504 to ADSP-BF592 Device Family to AD5415 Interface
Section, Figure 41, and Figure 42.................................................. 22
Changes to MC68HC11 to AD5415 Interface Section and
PIC16C6x/PIC16C7x to AD5415 Interface Section .................. 23
Changes to Overview of the AD5424 to AD5547 Devices
Section Title...................................................................................... 25
5/13—Rev. D to Rev. E
Changes to General Description .................................................... 1
Change to Ordering Guide............................................................ 26
5/12—Rev. C to Rev. D
Changes SDO Control (SDO1 and SDO2) Section ................... 20
6/11—Rev. B to Rev. C
Changes to General Description ................................................... 1
Deleted Evaluation Board for the DAC Section and Power
Supplies for the Evaluation Board Section.................................. 24
Changes to Ordering Guide .......................................................... 26
7/04—Revision 0: Initial Version
4/10—Rev. A to Rev. B
Added Figure 4.................................................................................. 6
Rev. F | Page 2 of 27
Data Sheet
AD5415
SPECIFICATIONS
VDD = 2.5 V to 5.5 V, VREF = 10 V, IOUT2 = 0 V. Temperature range for Y version: −40°C to +125°C. All speciꢀcations TMIN to TMAX, unless
otherwise noted. DC performance is measured with OP177, and ac performance is measured with AD8038, unless otherwise noted.
Table 1.1
Parameter
Min
Typ
Max
Unit
Test Conditions/Comments
Guaranteed monotonic
STATIC PERFORMANCE
Resolution
12
1
Bits
LSB
Relative Accuracy
Differential Nonlinearity
Gain Error
−1/+2 LSB
2ꢀ
mV
Gain Error Temperature Coefficient
Bipolar Zero Code Error
Output Leakage Current
ꢀ
ppm FSR/°C
2ꢀ
1
mV
nA
nA
Data = 0x0000, TA = 2ꢀ°C, IOUT
1
1ꢀ
Data = 0x0000, TA = −40°C to +12ꢀ°C, IOUT1
REFERENCE INPUT
Reference Input Range
VREFA, VREFB Input Resistance
10
10
V
8
13
kΩ
Input resistance temperature coefficient (TC) =
−ꢀ0 ppm/°C
VREFA to VREFB Input Resistance
Mismatch
1.6
2.ꢀ
%
Typ = 2ꢀ°C, max = 12ꢀ°C
R1, RFB Resistance
R2, R3 Resistance
R2 to R3 Resistance Mismatch
Input Capacitance
Code 0
17
17
20
2ꢀ
kΩ
kΩ
%
Input resistance TC = −ꢀ0 ppm/°C
Input resistance TC = −ꢀ0 ppm/°C
Typ = 2ꢀ°C, max = 12ꢀ°C
20
2ꢀ
0.06
0.18
3.ꢀ
3.ꢀ
pF
pF
Code 409ꢀ
DIGITAL INPUTS/OUTPUT
Input High Voltage, VIH
1.7
1.7
V
VDD = 3.6 V to ꢀ.ꢀ V
V
VDD = 2.ꢀ V to 3.6 V
Input Low Voltage, VIL
Output High Voltage, VOH
Output Low Voltage, VOL
0.8
0.7
V
VDD = 2.7 V to ꢀ.ꢀ V
V
VDD = 2.ꢀ V to 2.7 V
VDD − 1
V
VDD = 4.ꢀ V to ꢀ.ꢀ V, ISOURCE = 200 µA
VDD = 2.ꢀ V to 3.6 V, ISOURCE = 200 µA
VDD = 4.ꢀ V to ꢀ.ꢀ V, ISINK = 200 µA
VDD = 2.ꢀ V to 3.6 V, ISINK = 200 µA
VDD − 0.ꢀ
V
0.4
0.4
1
V
V
Input Leakage Current, IIL
Input Capacitance
µA
pF
4
10
DYNAMIC PERFORMANCE
Reference Multiplying Bandwidth (BW)
Output Voltage Settling Time
10
MHz
VREF = 3.ꢀ V p-p, DAC loaded all 1s
RLOAD = 100 Ω, CLOAD = 1ꢀ pF, VREF = 10 V
DAC latch alternately loaded with 0s and 1s
Measured to 1 mV of Full Scale (FS)
Measured to 4 mV of FS
Measured to 16 mV of FS
Digital Delay
80
3ꢀ
30
20
1ꢀ
3
120
70
ns
ns
60
ns
40
ns
10% to 90% Settling Time
Digital-to-Analog Glitch Impulse
Multiplying Feedthrough Error
30
ns
Rise and fall times
nV-sec
1 LSB change around major carry, VREF = 0 V
DAC latches loaded with all 0s, VREF = 3.ꢀ V
1 MHz
70
48
17
30
dB
dB
pF
pF
10 MHz
Output Capacitance
12
2ꢀ
DAC latches loaded with all 0s
DAC latches loaded with all 1s
Rev. F | Page 3 of 27
AD5415
Data Sheet
Parameter
Min
Typ
Max
Unit
Test Conditions/Comments
Digital Feedthrough
3
ꢀ
nV-sec
Feedthrough to DAC output with CS high and
alternate loading of all 0s and all 1s
At 1 kHz
Output Noise Spectral Density
Analog THD
2ꢀ
nV/√Hz
81
dB
VREF =3. 5 V p-p, all 1s loaded, f = 1 kHz
Clock = 10 MHz, VREF = 3.5 V
Digital THD
100 kHz fOUT
61
66
dB
dB
50 kHz fOUT
SFDR Performance (Wide Band)
Clock = 10 MHz
500 kHz fOUT
VREF = 3.5 V
55
63
65
dB
dB
dB
100 kHz fOUT
50 kHz fOUT
Clock = 25 MHz
500 kHz fOUT
50
60
62
dB
dB
dB
100 kHz fOUT
50 kHz fOUT
SFDR Performance (Narrow Band)
Clock = 10 MHz
500 kHz fOUT
VREF = 3.5 V
73
80
87
dB
dB
dB
100 kHz fOUT
50 kHz fOUT
Clock = 25 MHz
500 kHz fOUT
70
75
80
dB
dB
dB
100 kHz fOUT
50 kHz fOUT
Intermodulation Distortion
f1 = 40 kHz, f2 = 50 kHz
f1 = 40 kHz, f2 = 50 kHz
POWER REQUIREMENTS
Power Supply Range
IDD
VREF = 3.5 V
72
65
dB
dB
Clock = 10 MHz
Clock = 25 MHz
2.5
5.5
V
0.7
μA
μA
%/%
TA = 25°C, logic inputs = 0 V or VDD
TA = −40°C to +125°C, logic inputs = 0 V or VDD
∆VDD = 5%
0.5
10
Power Supply Sensitivity
0.001
1 Guaranteed by design and characterization, not subject to production test.
Rev. F | Page 4 of 27
Data Sheet
AD5415
TIMING CHARACTERISTICS
All input signals are specified with tr = tf = 1 ns (10% to 90% of VDD) and timed from a voltage level of (VIL + VIH)/2. VDD = 2.5 V to 5.5 V,
REF = 10 V, IOUT2 = 0 V, temperature range for Y version: −40°C to +125°C. All specifications TMIN to TMAX, unless otherwise noted.
V
Table 2.
Parameter1
Limit at TMIN, TMAX
Unit
Test Conditions/Comments2
Maximum clock frequency
fSCLK
t1
50
20
8
MHz max
ns min
ns min
ns min
ns min
ns min
ns min
ns min
ns min
ns min
ns min
ns min
ns min
ns min
MSPS
SCLK cycle time
t2
SCLK high time
t3
8
SCLK low time
t4
13
5
SYNC falling edge to SCLK falling edge setup time
Data setup time
t5
t6
4
Data hold time
t7
5
SYNC rising edge to SCLK falling edge
Minimum SYNC high time
t8
30
0
t9
SCLK falling edge to LDAC falling edge
LDAC pulse width
t10
t11
12
10
25
60
2.47
SCLK falling edge to LDAC rising edge
SCLK active edge to SDO valid, strong SDO driver
SCLK active edge to SDO valid, weak SDO driver
Consists of cycle time, SYNC high time, data setup, and output voltage settling time
3
t12
Update Rate
1 Guaranteed by design and characterization, not subject to production test.
2 Falling or rising edge as determined by the control bits of the serial word. Strong or weak SDO driver selected via the control register.
3 Daisy-chain and readback modes cannot operate at maximum clock frequency. SDO timing specifications measured with a load circuit, as shown in Figure 5.
t1
SCLK
t2
t3
t4
t8
t7
SYNC
DIN
t6
t5
DB0
DB15
t10
t9
1
LDAC
t11
2
LDAC
1
ASYNCHRONOUS LDAC UPDATE MODE.
SYNCHRONOUS LDAC UPDATE MODE.
2
NOTES
ALTERNATIVELY, DATA CAN BE CLOCKED INTO THE INPUT SHIFT REGISTER ON THE RISING EDGE OF SCLK AS
DETERMINED BY THE CONTROL BITS. TIMING IS AS ABOVE, WITH SCLK INVERTED.
Figure 2. Standalone Mode Timing Diagram
Rev. F | Page 5 of 27
AD5415
Data Sheet
t1
SCLK
SYNC
t2
t3
t7
t4
t6
t8
t5
DB0
(N + 1)
DB15
(N)
DB0
(N)
DB15
(N + 1)
SDIN
t12
DB0
(N)
DB15
(N)
SDO
NOTES
1. ALTERNATIVELY, DATA CAN BE CLOCKED INTO THE INPUT SHIFT REGISTER ON THE RISING EDGE OF SCLK AS
DETERMINED BY THE CONTROL BITS. IN THIS CASE, DATA IS CLOCKED OUT OF SDO ON THE FALLING
EDGE OF SCLK. TIMING IS AS ABOVE, WITH SCLK INVERTED.
Figure 3. Daisy-Chain Timing Diagram
SCLK
16
32
SYNC
DB15
DB0
DB15
DB0
SDIN
SDO
INPUT WORD SPECIFIES
REGISTER TO BE READ
NOP CONDITION
DB15
DB0
SELECTED REGISTER DATA
CLOCKED OUT
UNDEFINED
Figure 4. Readback Mode Timing Diagram
200µA
I
OL
V
(MIN) + V (MAX)
OL
OH
TO OUTPUT
PIN
2
C
L
50pF
200µA
I
OH
Figure 5. Load Circuit for SDO Timing Specifications
Rev. F | Page 6 of 27
Data Sheet
AD5415
ABSOLUTE MAXIMUM RATINGS
Transient currents of up to 100 mA do not cause SCR latch-up.
TA = 25°C, unless otherwise noted.
Stresses at or above those listed under Absolute Maximum
Ratings may cause permanent damage to the product. This is a
stress rating only; functional operation of the product at these
or any other conditions above those indicated in the operational
section of this specification is not implied. Operation beyond
the maximum operating conditions for extended periods may
affect product reliability.
Table 3.
Parameter
Rating
VDD to GND
−0.3 V to +7 V
−12 V to +12 V
−0.3 V to +7 V
10 mA
VREF, RFB to GND
IOUT1, IOUT2 to GND
ESD CAUTION
Input Current to Any Pin Except Supplies
Logic Inputs and Output1
Operating Temperature Range
Extended (Y Version)
−0.3 V to VDD + 0.3 V
−40°C to +125°C
−65°C to +150°C
150°C
Storage Temperature Range
Junction Temperature
24-Lead TSSOP, θJA Thermal Impedance
Lead Temperature, Soldering (10 sec)
128°C/W
300°C
Infrared (IR) Reflow, Peak Temperature
(<20 sec)
235°C
1 Overvoltages at SCLK,
, and SDIN are clamped by internal diodes.
SYNC
Rev. F | Page 7 of 27
AD5415
Data Sheet
PIN CONFIGURATION AND FUNCTION DESCRIPTIONS
1
24
23
22
21
20
19
18
17
16
15
14
13
I
1A
2A
I
I
1B
2B
OUT
OUT
OUT
2
I
OUT
3
R
A
R
B
FB
FB
4
R1A
R2A
R1B
R2B
5
AD5415
TOP VIEW
(Not to Scale)
6
R2_3A
R3A
R2_3B
R3B
7
8
V
A
V
V
B
REF
REF
DD
GND
9
10
11
12
LDAC
SCLK
SDIN
CLR
SYNC
SDO
Figure 6. Pin Configuration
Table 4. Pin Function Descriptions
Pin No. Mnemonic Description
1
2
IOUT1A
IOUT2A
DAC A Current Output.
DAC A Analog Ground. This pin is normally tied to the analog ground of the system, but can be biased to achieve
single-supply operation.
3
RFBA
DAC Feedback Resistor Pin. This pin establishes voltage output for the DAC by connecting to an external
amplifier output.
4 to 7
R1A, R2A,
DAC A 4-Quadrant Resistors. These pins allow a number of configuration modes, including bipolar operation, with
R2_3A, R3A minimum external components.
8
VREF
A
DAC A Reference Voltage Input Pin.
Ground Pin.
9
GND
10
LDAC
Load DAC Input. This pin allows asynchronous or synchronous updates to the DAC output. The DAC is
asynchronously updated when this signal goes low. Alternatively, if this line is held permanently low, an automatic
or synchronous update mode is selected, whereby the DAC is updated on the 16th clock falling edge when the
device is in standalone mode, or on the rising edge of SYNC when in daisy-chain mode.
11
12
13
SCLK
SDIN
SDO
Serial Clock Input. By default, data is clocked into the input shift register on the falling edge of the serial clock
input. Alternatively, by means of the serial control bits, the device can be configured such that data is clocked into
the shift register on the rising edge of SCLK.
Serial Data Input. Data is clocked into the 16-bit input register on the active edge of the serial clock input. By default, on
power-up data is clocked into the shift register on the falling edge of SCLK. The control bits allow the user to change the
active edge to the rising edge.
Serial Data Output. This pin allows a number of devices to be daisy-chained. By default, data is clocked into the shift
register on the falling edge and clocked out via SDO on the rising edge of SCLK. Data is always clocked out on the
alternate edge to loading data to the shift register. Writing the readback control word to the shift register makes
the DAC register contents available for readback on the SDO pin; they are clocked out on the next 16 opposite clock
edges to the active clock edge.
14
15
SYNC
Active Low Control Input. This pin provides the frame synchronization signal for the input data. When SYNC goes
low, it powers on the SCLK and SDIN buffers, and the input shift register is enabled. Data is loaded into the shift
register on the active edge of the subsequent clocks. In standalone mode, the serial interface counts the clocks,
and data is latched into the shift register on the 16th active clock edge.
CLR
VDD
Active Low Control Input. This pin clears the DAC output, input, and DAC registers. Configuration mode allows the user
to enable the hardware CLR pin as a clear to zero scale or midscale as required.
16
17
Positive Power Supply Input. This device can be operated from a supply of 2.5 V to 5.5 V.
DAC B Reference Voltage Input Pin.
VREFB
18 to 21 R3B, R2_3B, DAC B 4-Quadrant Resistors. These pins allow a number of configuration modes, including bipolar operation, with
a minimum of external components.
R2B, R1B
22
23
24
RFBB
DAC B Feedback Resistor Pin. This pin establishes voltage output for the DAC by connecting to the external
amplifier output.
IOUT2B
IOUT1B
DAC B Analog Ground. This pin is normally tied to the analog ground of the system, but can be biased to achieve
single-supply operation.
DAC B Current Output.
Rev. F | Page 8 of 27
Data Sheet
AD5415
TYPICAL PERFORMANCE CHARACTERISTICS
1.0
–0.40
–0.45
–0.50
–0.55
–0.60
–0.65
–0.70
T
V
= 25°C
= 5V
A
T
V
V
= 25°C
A
0.8
0.6
DD
= 10V
REF
= 5V
DD
0.4
0.2
0
–0.2
–0.4
–0.6
–0.8
–1.0
MIN DNL
0
500
1000
1500
2000
2500
3000
3500
4000
2
3
4
5
6
7
8
9
10
CODE
REFERENCE VOLTAGE
Figure 10. DNL vs. Reference Voltage
Figure 7. Integral Nonlinearity (INL) vs. Code (12-Bit DAC)
5
4
1.0
0.8
T
V
V
= 25°C
A
= 10V
REF
= 5V
V
= 5V
DD
DD
3
0.6
2
0.4
1
0.2
0
0
V
= 2.5V
DD
–1
–2
–3
–4
–5
–0.2
–0.4
–0.6
–0.8
–1.0
V
= 10V
REF
–60 –40 –20
0
20
40
60
80
100 120 140
0
500
1000
1500
2000
2500
3000
3500
4000
TEMPERATURE (°C)
CODE
Figure 11. Gain Error vs. Temperature
Figure 8. Differential Nonlinearity (DNL) vs. Code (12-Bit DAC)
8
7
6
5
4
3
2
1
0
0.6
T
= 25°C
A
0.5
0.4
MAX INL
0.3
V
= 5V
DD
0.2
T
V
= 25°C
= 5V
A
0.1
DD
0
MIN INL
–0.1
–0.2
–0.3
V
= 3V
DD
V
= 2.5V
DD
2
3
4
5
6
7
8
9
10
1.5
2.0
2.5
3.0
3.5
4.0
4.5
5.0
0
0.5
1.0
INPUT VOLTAGE (V)
REFERENCE VOLTAGE
Figure 12. Supply Current vs. Logic Input Voltage
Figure 9. INL vs. Reference Voltage
Rev. F | Page 9 of 27
AD5415
Data Sheet
1.6
1.4
1.2
1.0
0.8
0.6
0.4
0.2
6
0
–6
T
= 25°C
ALL ON
DB11
DB10
DB9
DB8
DB7
DB6
DB5
DB4
DB3
A
LOADING
ZS TO FS
–12
–18
–24
–30
–36
–42
–48
–54
–60
–66
–72
–78
–84
–90
–96
–102
I
I
1 V = 5V
OUT
DD
1 V = 3V
OUT
DD
DB2
DB1
DB0
T
V
= 25°C
A
= 5V
DD
V
= 3.5V
= 1.8pF
REF
ALL OFF
C
COMP
AMP = AD8038
0
–40
1
10
100
1k
10k
100k
1M 10M 100M
–20
0
20
40
60
80
100
120
FREQUENCY (Hz)
TEMPERATURE (°C)
Figure 13. Iout1 Leakage Current vs. Temperature
Figure 16. Reference Multiplying Bandwidth vs. Frequency and Code
0.50
0.45
0.40
0.35
0.30
0.25
0.20
0.15
0.10
0.05
0
0.2
V
= 5V
DD
0
–0.2
–0.4
ALL 0s
ALL 1s
V
= 2.5V
DD
ALL 1s
ALL 0s
T
V
V
C
= 25°C
A
–0.6
–0.8
= 5V
DD
= 3.5V
REF
= 1.8pF
COMP
AMP = AD8038
1
10 100
1k
10k
100k
1M
10M
100M
–60 –40 –20
0
20
40
60
80
100 120 140
FREQUENCY (Hz)
TEMPERATURE (°C)
Figure 17. Reference Multiplying Bandwidth—All 1s Loaded
Figure 14. Supply Current vs. Temperature
3
14
12
10
8
T
V
= 25°C
A
T
= 25°C
A
= 5V
DD
LOADING ZS TO FS
V
= 5V
0
–3
–6
–9
DD
6
V
V
= 3V
DD
DD
4
V
V
V
V
V
= 2V, AD8038 C 1.47pF
REF
REF
REF
REF
REF
C
= 2.5V
= 2V, AD8038 C 1pF
C
= 0.15V, AD8038 C 1pF
C
2
= 0.15V, AD8038 C 1.47pF
C
= 3.51V, AD8038 C 1.8pF
C
0
10k
100k
1M
10M
100M
1
10
100
1k
10k
100k
1M
10M
100M
FREQUENCY (Hz)
FREQUENCY (Hz)
Figure 15. Supply Current vs. Update Rate
Figure 18. Reference Multiplying Bandwidth vs. Frequency
and Compensation Capacitor
Rev. F | Page 10 of 27
Data Sheet
AD5415
0.045
–60
–65
–70
–75
–80
–85
–90
0x7FF TO 0x800
T
V
= 25°C
= 0V
T = 25°C
A
A
0.040
0.035
0.030
0.025
0.020
0.015
0.010
0.005
0
V
= 3V
REF
AMP = AD8038
= 1.8pF
DD
V
= 5V
V
= 3.5V p-p
DD
REF
C
COMP
V
= 3V
DD
0x800 TO 0x7FF
= 3V
V
DD
–0.005
–0.010
V
= 5V
DD
0
20
40
60
80
100 120 140 160 180 200
TIME (ns)
1
10
100
1k
10k
100k
1M
FREQUENCY (Hz)
Figure 22. THD and Noise vs. Frequency
Figure 19. Midscale Transition, VREF = 0 V
100
80
60
40
20
0
–1.68
–1.69
–1.70
–1.71
–1.72
–1.73
–1.74
–1.75
–1.76
–1.77
T
V
= 25°C
= 3.5V
A
0x7FF TO 0x800
= 5V
MCLK = 1MHz
REF
AMP = AD8038
= 1.8pF
V
DD
C
COMP
MCLK = 200kHz
MCLK = 0.5MHz
V
= 3V
DD
V
= 5V
V
DD
= 3V
DD
T
V
= 25°C
A
= 3.5V
REF
0x800 TO 0x7FF
20 40 60
AMP = AD8038
100 120 140 160 180 200
fOUT (kHz)
0
20
40
60
80
0
80
100 120 140 160 180 200
TIME (ns)
Figure 20. Midscale Transition, VREF = 3.5 V
Figure 23. Wideband Spurious-Free Dynamic Range (SFDR) vs. fOUT Frequency
20
0
90
T
V
= 25°C
= 3V
A
DD
AMP = AD8038
80
MCLK = 5MHz
70
MCLK = 10MHz
–20
–40
–60
–80
–100
–120
60
50
FULL SCALE
ZERO SCALE
MCLK = 25MHz
40
30
20
T
V
= 25°C
A
10
0
= 3.5V
REF
AMP = AD8038
1
100
1k
10k
100k
1M
10M
10
0
100 200 300 400 500 600 700 800 900 1000
fOUT (kHz)
FREQUENCY (Hz)
Figure 24. Wideband SFDR vs. fOUT Frequency
Figure 21. Power Supply Rejection Ratio vs. Frequency
Rev. F | Page 11 of 27
AD5415
Data Sheet
0
–10
–20
–30
–40
–50
–60
–70
–80
–90
–100
0
–10
–20
–30
–40
–50
–60
–70
–80
T
V
= 25°C
T = 25°C
A
DD
AMP = AD8038
65k CODES
A
= 5V
V
= 3V
DD
AMP = AD8038
65k CODES
–90
0
2
4
6
8
10
12
250 300 350 400 450 500 550 600 650 700 750
FREQUENCY (MHz)
FREQUENCY (kHz)
Figure 25. Wideband SFDR, fOUT = 100 kHz, Clock = 25 MHz
Figure 28. Narrow-Band Spectral Response, fOUT = 500 kHz, Clock = 25 MHz
20
0
–10
–20
–30
–40
–50
–60
–70
–80
–90
–100
T
V
= 25°C
T
V
= 25°C
A
A
= 5V
= 3V
DD
DD
AMP = AD8038
65k CODES
AMP = AD8038
65k CODES
0
–20
–40
–60
–80
–100
–120
0
0.5
1.0
1.5
2.0
2.5
3.0
3.5
4.0
4.5
5.0
50
60
70
80
90
100 110 120 130 140 150
FREQUENCY (kHz)
FREQUENCY (MHz)
Figure 26. Wideband SFDR, fOUT = 500 kHz, Clock = 10 MHz
Figure 29. Narrow-Band SFDR, fOUT = 100 kHz, MCLK = 25 MHz
0
0
–10
–20
–30
–40
–50
–60
–70
–80
–90
T
V
= 25°C
T = 25°C
A
DD
AMP = AD8038
65k CODES
A
= 5V
V
= 3V
DD
–10
–20
–30
–40
–50
–60
–70
–80
–90
–100
AMP = AD8038
65k CODES
0
0.5
1.0
1.5
2.0
2.5
3.0
3.5
4.0
4.5
5.0
70
75
80
85
90
95
100 105 110 115 120
FREQUENCY (MHz)
FREQUENCY (kHz)
Figure 27. Wideband SFDR, fOUT = 50 kHz, Clock = 10 MHz
Figure 30. Narrow-Band Intermodulation Distortion (IMD), fOUT = 90 kHz,
100 kHz, Clock = 10 MHz
Rev. F | Page 12 of 27
Data Sheet
AD5415
300
250
200
150
100
50
0
–10
–20
–30
–40
–50
–60
–70
–80
–90
–100
T
= 25°C
T
V
= 25°C
A
A
ZERO SCALE LOADED TO DAC
MIDSCALE LOADED TO DAC
FULL SCALE LOADED TO DAC
AMP = AD8038
= 5V
DD
AMP = AD8038
65k CODES
0
100
1k
10k
FREQUENCY (Hz)
100k
0
50
100
150
200
250
300
350
400
FREQUENCY (kHz)
Figure 31. Wideband IMD, fOUT = 90 kHz, 100 kHz, Clock = 25 MHz
Figure 32. Output Noise Spectral Density
Rev. F | Page 13 of 27
AD5415
Data Sheet
TERMINOLOGY
Relative Accuracy (Endpoint Nonlinearity)
A measure of the maximum deviation from a straight line
passing through the endpoints of the DAC transfer function. It
is measured after adjusting for zero scale and full scale and is
normally expressed in LSB or as a percentage of the full-scale
reading.
Digital Crosstalk
The glitch impulse transferred to the outputs of one DAC in
response to a full-scale code change (all 0s to all 1s, or vice
versa) in the input register of the other DAC. It is expressed
in nV-sec.
Analog Crosstalk
Differential Nonlinearity
The glitch impulse transferred to the output of one DAC due to
a change in the output of another DAC. It is measured by
loading one of the input registers with a full-scale code change
The difference in the measured change and the ideal 1 LSB
change between two adjacent codes. A specified differential
nonlinearity of −1 LSB maximum over the operating
temperature range ensures monotonicity.
LDAC
(all 0s to all 1s, or vice versa) while keeping
high and
low and monitoring the output of the DAC
LDAC
then pulsing
whose digital code has not changed. The area of the glitch is
expressed in nV-sec.
Gain Error (Full-Scale Error)
A measure of the output error between an ideal DAC and the
actual device output. For this DAC, ideal maximum output is
Channel-to-Channel Isolation
V
REF − 1 LSB. The gain error of the DAC is adjustable to zero
The portion of input signal from a DAC reference input that
appears at the output of another DAC. It is expressed in decibels.
with an external resistance.
Output Leakage Current
Total Harmonic Distortion (THD)
The current that flows into the DAC ladder switches when they
are turned off. For the IOUT1 terminal, it can be measured by
loading all 0s to the DAC and measuring the IOUT1 current.
Minimum current flows into the IOUT2 line when the DAC is
loaded with all 1s.
The DAC is driven by an ac reference. The ratio of the rms sum
of the harmonics of the DAC output to the fundamental value is
the THD. Usually only the lower-order harmonics are included,
such as the second to fifth harmonics.
2
2
2
2
V2 +V3 +V4 +V5
Output Capacitance
THD = 20 log
V1
Capacitance from IOUT1 or IOUT2 to AGND.
Intermodulation Distortion (IMD)
Output Current Settling Time
The DAC is driven by two combined sine wave references of
frequencies fa and fb. Distortion products are produced at sum
and difference frequencies of mfa nfb, where m, n = 0, 1, 2, 3 ...
Intermodulation terms are those for which m or n is not equal
to 0. The second-order terms include (fa + fb) and (fa − fb), and
the third-order terms are (2fa + fb), (2fa − fb), (f + 2fa + 2fb), and
(fa − 2fb). IMD is defined as
The amount of time for the output to settle to a specified level
for a full-scale input change. For this device, it is specified with
a 100 Ω resistor to ground.
Digital-to-Analog Glitch Impulse
The amount of charge injected from the digital inputs to the
analog output when the inputs change state. This is normally
specified as the area of the glitch in either pA-sec or nV-sec,
depending on whether the glitch is measured as a current or
voltage signal.
(rms sum of the sum and diff distortion products)
IMD = 20 log
rms amplitude of the fundamental
Digital Feedthrough
When the device is not selected, high frequency logic activity on
the digital inputs of the device is capacitively coupled through the
device and produces noise on the IOUT pins and, subsequently, on
the following circuitry. This noise is digital feedthrough.
Compliance Voltage Range
The maximum range of (output) terminal voltage for which the
device provides the specified characteristics.
Multiplying Feedthrough Error
The error due to capacitive feedthrough from the DAC
reference input to the DAC IOUT1 terminal when all 0s are
loaded to the DAC.
Rev. F | Page 14 of 27
Data Sheet
AD5415
GENERAL DESCRIPTION
DAC SECTION
When an output amplifier is connected in unipolar mode, the
output voltage is given by
The AD5415 is a 12-bit, dual-channel, current output DAC
consisting of standard inverting R-2R ladder configuration.
Figure 33 shows a simplified diagram of a single channel of the
AD5415. The feedback resistor RFB has a value of 2R. The value
of R is typically 10 kΩ (with a minimum of 8 kΩ and a maximum
of 12 kΩ). If IOUT1 and IOUT2 are kept at the same potential, a
constant current flows into each ladder leg, regardless of the
digital input code. Therefore, the input resistance presented at
V
OUT = −VREF × D/2n
where:
D is the fractional representation, in the range of 0 to 4,095, of
the digital word loaded to the DAC.
n is the number of bits.
Note that the output voltage polarity is opposite the VREF
polarity for dc reference voltages. This DAC is designed to
operate with either negative or positive reference voltages. The
V
REF is always constant.
R
R
R
V
A
REF
VDD power pin is only used by the internal digital logic to drive
2R
S1
2R
S2
2R
S3
2R
2R
the on and off states of the DAC switches.
R
S12
R
A
This DAC is also designed to accommodate ac reference input
signals in the range of −10 V to +10 V.
FB
I
1A
OUT
OUT
I
2A
With a fixed 10 V reference, the circuit in Figure 34 gives a
unipolar 0 V to −10 V output voltage swing. When VIN is an
ac signal, the circuit performs 2-quadrant multiplication.
DAC DATA LATCHES
AND DRIVERS
Figure 33. Simplified Ladder
Table 5 shows the relationship between digital code and
expected output voltage for unipolar operation.
Access is provided to the VREF, RFB, IOUT1, and IOUT2 terminals of
the DAC, making the device extremely versatile and allowing it
to be configured in several operating modes, such as unipolar
output, bipolar output, or single-supply mode.
Table 5. Unipolar Code
Digital Input
Analog Output (V)
−VREF (4,095/4,096)
−VREF (2,048/4,096) = −VREF/2
−VREF (1/4,096)
1111 1111 1111
1000 0000 0000
0000 0000 0001
0000 0000 0000
CIRCUIT OPERATION
Unipolar Mode
Using a single operational amplifier, this device can easily be
configured to provide 2-quadrant multiplying operation or a
unipolar output voltage swing, as shown in Figure 34.
−VREF (0/4,096) = 0
V
DD
R1A
R
R1
2R
FB
2R
R
A
FB
R2A
R2_3A
R3A
C1
I
1A
R2
2R
OUT
AD5415
12-BIT DAC A
R
A1
V
= 0V TO –V
IN
OUT
I
2A
OUT
R3
2R
AGND
V
A
SYNC SCLK SDIN
GND
AGND
REF
AGND
µCONTROLLER
NOTES
1. DAC B OMITTED FOR CLARITY.
2. C1 PHASE COMPENSATION (1pF TO 2pF) MAY BE REQUIRED
IF A1 IS A HIGH SPEED AMPLIFIER.
Figure 34. Unipolar Operation
Rev. F | Page 15 of 27
AD5415
Data Sheet
V
DD
Bipolar Operation
R1A
R
R1
2R
FB
2R
R
A
In some applications, it may be necessary to generate full
4-quadrant multiplying operation or a bipolar output swing.
This can easily be accomplished by using another external
amplifier and the on-chip 4-quadrant resistors, as shown in
Figure 35.
FB
R2A
R2_3A
R3A
V
IN
C1
I
1A
R2
2R
OUT
AD5415
12-BIT DAC A
R
A1
V
= –V TO +V
IN IN
OUT
I
2A
OUT
R3
2R
A1
AGND
When in bipolar mode, the output voltage is given by
V
A
SYNC SCLK SDIN
GND
REF
OUT = (VREF × D/2n − 1) − VREF
AGND
V
AGND
µCONTROLLER
where:
NOTES
1. DAC B OMITTED FOR CLARITY.
2. C1 PHASE COMPENSATION (1pF TO 2pF) MAY BE REQUIRED
IF A1 IS A HIGH SPEED AMPLIFIER.
D is the fractional representation, in the range of 0 to 4,095, of
the digital word loaded to the DAC.
n is the number of bits.
Figure 35. Bipolar Operation
When VIN is an ac signal, the circuit performs 4-quadrant
multiplication.
SINGLE-SUPPLY APPLICATIONS
Voltage Switching Mode of Operation
Table 6 shows the relationship between digital code and the
expected output voltage for bipolar operation.
Figure 36 shows the DAC operating in the voltage switching
mode. The reference voltage, VIN, is applied to the IOUT1A pin,
I
OUT2A is connected to AGND, and the output voltage is
Table 6. Bipolar Code
available at the VREFA terminal. In this configuration, a positive
reference voltage results in a positive output voltage, making
single-supply operation possible. The output from the DAC is
voltage at a constant impedance (the DAC ladder resistance).
Therefore, an operational amplifier is necessary to buffer the
output voltage. The reference input no longer sees a constant
input impedance, but one that varies with code. Therefore, the
voltage input must be driven from a low impedance source.
Digital Input
Analog Output (V)
+VREF (4095/4096)
0
1111 1111 1111
1000 0000 0000
0000 0000 0001
0000 0000 0000
−VREF (4095/4096)
−VREF (4096/4096)
Stability
In the I-to-V configuration, the IOUT of the DAC and the inverting
node of the operational amplifier must be connected as close as
possible, and proper printed circuit board (PCB) layout techniques
must be used. Because every code change corresponds to a step
function, gain peaking may occur if the operational amplifier has
limited gain bandwidth product (GBP) and there is excessive par-
asitic capacitance at the inverting node. This parasitic capacitance
introduces a pole into the open-loop response, which can cause
ringing or instability in the closed-loop applications circuit.
V
DD
R
R
1
2
R
A
V
FB
DD
I
1A
V
OUT
IN
V
OUT
V
A
REF
I
2A
OUT
GND
NOTES
1. SIMILAR CONFIGURATION FOR DACB
An optional compensation capacitor, C1, can be added in parallel
with RFBA for stability, as shown in Figure 34 and Figure 35. Too
small a value of C1 can produce ringing at the output, whereas
too large a value can adversely affect the settling time. C1 must
be found empirically, but 1 pF to 2 pF is generally adequate for
the compensation.
2. C1 PHASE COMPENSATION (1pF TO 2pF) MAY BE REQUIRED
IF A1 IS A HIGH SPEED AMPLIFIER.
Figure 36. Single-Supply Voltage Switching Mode
Note that VIN is limited to low voltages because the switches in
the DAC ladder no longer have the same source-drain drive
voltage. As a result, the on resistance differs and degrades the
integral linearity of the DAC. Also, VIN must not go negative by
more than 0.3 V or an internal diode turns on, causing the device
to exceed the maximum ratings. In this type of application, the
full range of multiplying capability of the DAC is lost.
Rev. F | Page 16 of 27
Data Sheet
AD5415
V
V
DD
ADDING GAIN
V
IN
In applications where the output voltage must be greater than VIN,
gain can be added with an additional external amplifier or it can
be achieved in a single stage. Consider the effect of temperature
coefficients of the thin film resistors of the DAC. Simply placing
a resistor in series with the RFB resistor causes mismatches in the
temperature coefficients, resulting in larger gain temperature
coefficient errors. Instead, the circuit in Figure 37 shows the
recommended method for increasing the gain of the circuit. R1,
R2, and R3 can have similar temperature coefficients, but they
need not match the temperature coefficients of the DAC. This
approach is recommended in circuits where gains greater than 1
are required. Note that RFB ≫ R2//R3 and a gain error percentage of
100 × (R2//R3)/RFB must be taken into consideration.
R
A
FB
DD
I
1A
OUT
V
A
REF
I
2A
OUT
GND
V
OUT
NOTES
1. ADDITIONAL PINS OMITTED FOR CLARITY.
Figure 38. Current Steering DAC Used as a Divider or
Programmable Gain Element
As D is reduced, the output voltage increases. For small values
of the digital fraction, D, it is important to ensure the amplifier does
not saturate and the required accuracy is met. For example, an 8-bit
DAC driven with the binary code 0x10 (0001 0000)—that is,
16 decimal—in the circuit of Figure 38 must cause the output
voltage to be 16 times VIN. However, if the DAC has a linearity
specification of 0.5 LSB, D can have a weight in the range of
15.5/256 to 16.5/256, so that the possible output voltage is in the
range of 15.5 VIN to 16.5 VIN—an error of 3%, even though the
DAC itself has a maximum error of 0.2%.
V
DD
C1
V
R
A
DD
FB
I
1A
2A
OUT
R1
V
V
OUT
12-BIT DAC
GND
V
A
IN
REF
I
OUT
R3
R2
R2 + R3
R2
GAIN =
R2R3
R2 + R3
R1 =
NOTES
1. ADDITIONAL PINS OMITTED FOR CLARITY.
2. C1 PHASE COMPENSATION (1pF TO 2pF) MAY BE REQUIRED
IF A1 IS A HIGH SPEED AMPLIFIER.
DAC leakage current is also a potential source of errors in
divider circuits. The leakage current must be counterbalanced by
an opposite current supplied from the operational amplifier
through the DAC. Because only a fraction, D, of the current into
the VREFA terminal is routed to the IOUT1A terminal, the output
voltage changes as follows:
Figure 37. Increasing the Gain of the Current Output DAC
DIVIDER OR PROGRAMMABLE GAIN ELEMENT
Current steering DACs are very flexible and lend themselves to
many applications. If this type of DAC is connected as the feedback
element of an operational amplifier and RFB is used as the input
resistor, as shown in Figure 38, the output voltage is inversely
proportional to the digital input fraction, D.
Output Error Voltage Due to DAC Leakage = (Leakage × R)/D
where R is the DAC resistance at the VREFA terminal.
For D, which is equal to 1 − 2−n, the output voltage is
For a DAC leakage current of 10 nA, R = 10 kΩ, and a gain (that
is, 1/D) of 16, the error voltage is 1.6 mV.
VOUT = −VIN/D = −VIN/(1 − 2−n)
Rev. F | Page 17 of 27
AD5415
Data Sheet
This output voltage change is superimposed on the desired
REFERENCE SELECTION
change in output between the two codes and gives rise to a
differential linearity error, which, if large enough, might cause
the DAC to be nonmonotonic.
When selecting a reference for use with the AD5415 and other
devices in this series of current output DACs, pay attention to
the reference output voltage temperature coefficient specification.
This parameter not only affects the full-scale error, but also can
affect the linearity (INL and DNL) performance. The reference
temperature coefficient must be consistent with the system
accuracy specifications. For example, an 8-bit system required
to hold the overall specification within 1 LSB over the temp-
erature range 0°C to 50°C dictates that the maximum system
drift with temperature must be less than 78 ppm/°C. A 12-bit
system with the same temperature range to overall specification
within 2 LSB requires a maximum drift of 10 ppm/°C. Choosing
a precision reference with a low output temperature coefficient
minimizes this error source. Table 7 lists some of the references
available from Analog Devices, Inc., that are suitable for use
with this range of current output DACs.
The input bias current of an operational amplifier also generates
an offset at the voltage output as a result of the bias current flowing
in the feedback resistor, RFB. Most operational amplifier s have
input bias currents low enough to prevent significant errors in
12-bit applications.
Common-mode rejection of the operational amplifier is
important in voltage switching circuits, because it produces a
code dependent error at the voltage output of the circuit. Most
operational amplifier s have adequate common-mode rejection
for use at 12-bit resolution.
Provided that the DAC switches are driven from true wideband
low impedance sources (VIN and AGND), they settle quickly.
Consequently, the slew rate and settling time of a voltage switching
DAC circuit is largely determined by the output operational
amplifier. To obtain minimum settling time in this configuration,
minimize capacitance at the VREF node (the voltage output node
in this application) of the DAC. This is done by using low input
capacitance buffer amplifiers and careful board design.
AMPLIFIER SELECTION
The primary requirement for the current steering mode is an
amplifier with low input bias currents and low input offset voltage.
Because of the code dependent output resistance of the DAC,
the input offset voltage of an operational amplifier is multiplied
by the variable gain of the circuit. A change in this noise gain
between two adjacent digital fractions produces a step change in
the output voltage due to the amplifier input offset voltage.
Most single-supply circuits include ground as part of the analog
signal range, which in turn requires an amplifier that can handle
rail-to-rail signals. Analog Devices offers a wide range of single-
supply amplifiers, as listed in Table 8 and Table 9.
Rev. F | Page 18 of 27
Data Sheet
AD5415
Table 7. Suitable Analog Devices Precision References
Part No. Output Voltage (V)
Initial Tolerance (%)
Temp Drift (ppm/°C)
ISS (mA)
Output Noise (µV p-p) Package
ADR01
ADR01
ADR02
ADR02
ADR03
ADR03
ADR06
ADR06
ADR431
ADR435
ADR391
ADR395
10
10
5
0.05
0.05
0.06
0.06
0.10
0.10
0.10
0.10
0.04
0.04
0.16
0.10
3
9
3
9
3
9
3
9
3
3
9
9
1
20
20
10
10
6
SOIC-8
1
TSOT-23, SC70
SOIC-8
1
5
1
TSOT-23, SC70
SOIC-8
2.5
2.5
3
1
1
6
TSOT-23, SC70
SOIC-8
1
10
10
3.5
8
3
1
TSOT-23, SC70
SOIC-8
2.5
5
0.8
0.8
0.12
0.12
SOIC-8
2.5
5
5
TSOT-23
8
TSOT-23
Table 8. Suitable Analog Devices Precision Operational Amplifiers
Part No. Supply Voltage (V) VOS (Max) (µV) IB (Max) (nA) 0.1 Hz to 10 Hz Noise (µV p-p)
Supply Current (µA)
Package
OP97
2 to 20
25
60
5
0.1
0.5
0.4
1
600
500
975
50
SOIC-8
OP1177
2.5 to 15
2
MSOP, SOIC-8
MSOP, SOIC-8
TSOT
AD8551 2.7 to 5
AD8603 1.8 to 6
AD8628 2.7 to 6
0.05
0.001
0.1
50
5
2.3
0.5
850
TSOT, SOIC-8
Table 9. Suitable Analog Devices High Speed Operational Amplifiers
Part No.
AD8065
AD8021
AD8038
AD9631
Supply Voltage (V)
5 to 24
BW at ACL (MHz)
Slew Rate (V/µs)
VOS (Max) (µV) IB (Max) (nA)
Package
145
490
350
320
180
1,500
1,000
3,000
10,000
6,000
10,500
750
SOIC-8, SOT-23, MSOP
SOIC-8, MSOP
SOIC-8, SC70-5
SOIC-8
2.5 to 12
3 to 12
120
425
3 to 6
1,300
7,000
Rev. F | Page 19 of 27
AD5415
Data Sheet
SDO Control (SDO1 and SDO2)
SERIAL INTERFACE
The SDO bits enable the user to control the SDO output driver
strength, disable the SDO output, or configure it as an open-
drain driver. The strength of the SDO driver affects the timing
of t12 and, when stronger, allows a faster clock cycle to be used.
Note that when the SDO output is disabled the daisy-chain
mode is also disabled.
The AD5415 has an easy to use 3-wire interface that is
compatible with SPI, QSPI, MICROWIRE, and most DSP
interface standards. Data is written to the device in 16-bit
words. Each 16-bit word consists of four control bits and
12 data bits, as shown in Figure 39.
Low Power Serial Interface
Table 10. SDO Control Bits
To minimize the power consumption of the device, the interface
only powers up fully when the device is being written to, that is,
SDO2
SDO1
Function
SYNC
on the falling edge of
. The SCLK and DIN input buffers
0
0
1
1
0
1
0
1
Full SDO driver
Weak SDO driver
SDO configured as open drain
Disable SDO output
SYNC
are powered down on the rising edge of
.
DAC Control Bits C3 to C0
Control Bits C3 to C0 allow control of various functions of the
DAC, as shown in Table 11. Default settings of the DAC at power
on are as follows. Data is clocked into the shift register on falling
clock edges, and daisy-chain mode is enabled. The device powers
on with a zero-scale load to the DAC register and IOUT lines. The
DAC control bits allow the user to adjust certain features at power
on. For example, daisy-chaining can be disabled when not in use,
an active clock edge can be changed to a rising edge, and DAC
output can be cleared to either zero scale or midscale. The user
can also initiate a readback of the DAC register contents for
verification purposes.
Daisy-Chain Control (DSY)
DSY enables or disables daisy-chain mode. A 1 enables daisy-
chain mode; a 0 disables it. When disabled, a readback request
is accepted, SDO is automatically enabled, the DAC register
contents of the relevant DAC are clocked out on SDO, and,
when complete, SDO is disabled again.
CLR
Hardware
Bit (HCLR)
CLR
The default setting for the hardware
pin is to clear the
registers and DAC output to zero code. A 1 in the HCLR bit
clears the DAC outputs to midscale; a 0 clears them to zero scale.
Control Register (Control Bits = 1101)
While maintaining software compatibility with single-channel
current output DACs (AD5426/AD5433/AD5443), this DAC
also features additional interface functionality. Simply set the
control bits to 1101 to enter control register mode. Figure 40
shows the contents of the control register, the functions of
which are described in the following sections.
Active Clock Edge (SCLK)
The default active clock edge is the falling edge. Write a 1 to this
bit to clock data in on the rising edge; write a 0 to clock it in on
the falling edge.
DB15 (MSB)
DB0 (LSB)
C3
C2
C1
C0
DB11 DB10
DB9
DB8
DB7
DB6
DB5
DB4
DB3
DB2
DB1
DB0
CONTROL BITS
DATA BITS
Figure 39. 12-Bit Input Shift Register Contents
DB15 (MSB)
1
DB0 (LSB)
X X
1
0
1
SDO1 SDO2
DSY HCLR SCLK
X
X
X
X
X
CONTROL BITS
Figure 40. Control Register Loading Sequence
Rev. F | Page 20 of 27
Data Sheet
AD5415
Table 11. DAC Control Bits
C3
0
0
0
0
0
0
0
0
1
1
1
1
1
1
1
1
C2
0
0
0
0
1
1
1
1
0
0
0
0
1
1
1
1
C1
0
0
1
1
0
0
1
1
0
0
1
1
0
0
1
1
C0
0
1
0
1
0
1
0
1
0
1
0
1
0
1
0
1
DAC
Function
A and B
No operation (power-on default)
Load and update
A
A
Initiate readback
A
Load input register
Load and update
B
B
Initiate readback
B
Load input register
Update DAC outputs
Load input registers
Disable daisy-chain
Clock data to shift register on rising edge
Clear DAC output to zero scale
Clear DAC output to midscale
Control word
A and B
A and B
–
–
–
–
–
–
–
Reserved
No operation
When control bits are 0000, the device is in no-operation mode.
This might be useful in daisy-chain applications where the user
does not want to change the settings of a particular DAC in the
chain. Write 0000 to the control bits for that DAC, and subsequent
data bits are ignored.
SYNC
Function
SYNC
is an edge triggered input that acts as a frame synchroni-
zation signal and chip enable. Data can only be transferred into
SYNC
the device while
is low. To start the serial data transfer,
SYNC
SYNC
falling
must be taken low, observing the minimum
Standalone Mode
to SCLK falling edge setup time, t4.
After power on, writing 1001 to the control word disables daisy-
Daisy-Chain Mode
SYNC
chain mode. The first falling edge of
counter to ensure that the correct number of bits are shifted in and
SYNC
resets the serial clock
Daisy-chain mode is the default mode at power on. To disable
the daisy-chain function, write 1001 to the control word. In
daisy-chain mode, the internal gating on SCLK is disabled.
SCLK is continuously applied to the input shift register when
out of the serial shift registers. A
edge during the 16-bit
write cycle causes the device to abort the current write cycle.
After the falling edge of the 16th SCLK pulse, data is automati-
cally transferred from the input shift register to the DAC. For
another serial transfer to take place, the counter must be reset
SYNC
is low. If more than 16 clock pulses are applied, the data
ripples out of the shift register and appears on the SDO line.
This data is clocked out on the rising edge of SCLK and is valid
for the next device on the falling edge of SCLK (default). By
connecting this line to the SDIN input on the next device in the
chain, a multidevice interface is constructed. For each device in
the system, 16 clock pulses are required. Therefore, the total
number of clock cycles must equal 16N, where N is the total
number of devices in the chain. (See Figure 5.)
SYNC
by the falling edge of
.
LDAC
Function
LDAC
The
function allows asynchronous and synchronous
updates to the DAC output. The DAC is asynchronously updated
when this signal goes low. Alternatively, if this line is held per-
manently low, an automatic or synchronous update mode is
selected, whereby the DAC is updated on the 16th clock falling
edge when the device is in standalone mode, or on the rising
SYNC
When the serial transfer to all devices is complete,
must be
taken high. This prevents additional data from being clocked
into the input shift register. A burst clock containing the exact
SYNC
edge of
Software
The load and update mode also functions as a software update
LDAC
when the device is in daisy-chain mode.
SYNC
number of clock cycles can be used, after which
is taken
, data is automatically trans-
ferred from each device input shift register to the addressed DAC.
LDAC
Function
SYNC
high. After the rising edge of
function, irrespective of the voltage level on the
pin.
Rev. F | Page 21 of 27
AD5415
Data Sheet
Table 12 shows the setup for the SPORT control register.
Table 12. SPORT Control Register Setup
MICROPROCESSOR INTERFACING
Microprocessor interfacing to the AD5415 DAC is through a
serial bus that uses standard protocol compatible with micro-
controllers and DSP processors. The communication channel is
a 3-wire interface consisting of a clock signal, a data signal, and
a synchronization signal. The AD5415 requires a 16-bit word,
with the default being data valid on the falling edge of SCLK;
however, this is changeable using the control bits in the data-word.
Name
TFSW
INVTFS
DTYPE
ISCLK
TFSR
Setting
Description
1
Alternate framing
Active low frame signal
Right justify data
Internal serial clock
Frame every word
Internal framing signal
16-bit data-word
1
00
1
1
ADSP-21xx to AD5415 Interface
ITFS
1
SLEN
1111
The ADSP-21xx family of DSPs is easily interfaced to the AD5415
DAC without the need for extra glue logic. Figure 41 is an example
of an SPI interface between the DAC and the ADSP-2191M. SCK
ADSP-BF504 to ADSP-BF592 Device Family to AD5415
Interface
of the DSP drives the serial data line, SDIN.
is driven
SYNC
The ADSP-BF504 to ADSP-BF592 device family of processors
has an SPI-compatible port that enables the processor to comm-
unicate with SPI-compatible devices. A serial interface between
the BlackFin® processor and the AD5415 DAC is shown in
Figure 43. In this configuration, data is transferred through the
from a port line, in this case
.
SPIxSEL
ADSP-2191M1
AD54151
SYNC
SPIxSEL
MOSI
SDIN
MOSI (master output, slave input) pin.
is driven by the
SYNC
SCK
SCLK
pin, which is a reconfigured programmable flag pin.
SPIxSEL
AD54151
1
ADSP-BF5xx1
ADDITIONAL PINS OMITTED FOR CLARITY.
Figure 41. ADSP-2191M SPI to AD5415 Interface
SYNC
SDIN
SPIxSEL
MOSI
A serial interface between the DAC and DSP SPORT is shown
in Figure 42. In this interface example, SPORT0 is used to transfer
data to the DAC shift register. Transmission is initiated by writing a
word to the Tx register after SPORT is enabled. In a write sequence,
data is clocked out on each rising edge of the DSP serial clock
and clocked into the DAC input shift register on the falling edge
of the SCLK. The update of the DAC output takes place on the
SCK
SCLK
1
ADDITIONAL PINS OMITTED FOR CLARITY.
Figure 43. ADSP-BF504 to ADSP-BF592 Device Family to AD5415 Interface
(ADSP-BFxx Denotes the ADSP-BF504 to ADSP-BF592)
The ADSP-BF504 to ADSP-BF592 device family processors
incorporates channel synchronous serial ports (SPORT). A serial
interface between the DAC and the DSP SPORT is shown in
Figure 44. When SPORT is enabled, initiate transmission by
writing a word to the Tx register. The data is clocked out on
each rising edge of the DSP serial clock and clocked into the
DAC input shift register on the falling edge of the SCLK. The
DAC output is updated by using the transmit frame synch-
rising edge of the
signal.
SYNC
ADSP-2191M1
AD54151
TFS
SYNC
DT
SDIN
SCLK
SCLK
ronization (TFS) line to provide a
signal.
SYNC
1
ADDITIONAL PINS OMITTED FOR CLARITY.
Figure 42. ADSP-2191M SPORT to AD5415 Interface
AD54151
ADSP-BF5xx1
Communication between two devices at a given clock speed is
possible when the following specifications are compatible: frame
sync delay and frame sync setup and hold, data delay and data
setup and hold, and SCLK width. The DAC interface expects a
TFS
DT
SYNC
SDIN
SCLK
SCLK
t4 (
falling edge to SCLK falling edge setup time) of 13 ns
SYNC
minimum. See the ADSP-21xx device family for information on
clock and frame frequencies for the SPORT register.
1
ADDITIONAL PINS OMITTED FOR CLARITY.
SYNC
Figure 44. ADSP-BF504 to ADSP-BF592 Device Family SPORT to AD5415 Interface
(ADSP-BFxx Denotes the ADSP-BF504 to ADSP-BF592)
Rev. F | Page 22 of 27
Data Sheet
AD5415
80C51/80L51 to AD5415 Interface
MC68HC111
AD54151
A serial interface between the DAC and the 80C51 is shown in
Figure 45. TxD of the 80C51 drives SCLK of the DAC serial
interface, and RxD drives the serial data line, SDIN. P1.1 is a
bit-programmable pin on the serial port and is used to drive
PC7
SCK
SYNC
SCLK
SDIN
MOSI
. When data is to be transmitted to the switch, P1.1 is
SYNC
1
ADDITIONAL PINS OMITTED FOR CLARITY.
taken low. The 80C51/80L51 only transmits data in 8-bit bytes;
therefore, only eight falling clock edges occur in the transmit
cycle. To load data correctly to the DAC, P1.1 is left low after
the first eight bits are transmitted, and a second write cycle is
initiated to transmit the second byte of data. Data on RxD is
clocked out of the microcontroller on the rising edge of TxD
and is valid on the falling edge of TxD. As a result, no glue logic
is required between the DAC and microcontroller interface.
P1.1 is taken high following the completion of this cycle. The
80C51 provides the LSB of the SBUF register as the first bit in
the data stream. The DAC input register requires the data with
the MSB as the first bit received. The transmit routine must take
this into account.
Figure 46. MC68HC11 to AD5415 Interface
If the user wants to verify the data previously written to the
input shift register, the SDO line can be connected to MISO of
the MC68HC11, and, with
low, the shift register clocks
SYNC
data out on the rising edges of SCLK.
MICROWIRE to AD5415 Interface
Figure 47 shows an interface between the DAC and any
MICROWIRE-compatible device. Serial data is shifted out on
the falling edge of the serial clock, SK, and is clocked into the
DAC input shift register on the rising edge of SK, which
corresponds to the falling edge of the DAC SCLK.
MICROWIRE1
AD54151
AD54151
80511
SK
SO
CS
SCLK
TxD
RxD
P1.1
SCLK
SDIN
SYNC
SDIN
SYNC
1
ADDITIONAL PINS OMITTED FOR CLARITY.
1
ADDITIONAL PINS OMITTED FOR CLARITY.
Figure 47. MICROWIRE to AD5415 Interface
Figure 45. 80C51/80L51 to AD5415 Interface
PIC16C6x/PIC16C7x to AD5415 Interface
MC68HC11 to AD5415 Interface
The PIC16C6x/PIC16C7x (Microchip) synchronous serial port
(SSP) is configured as an SPI master with the clock polarity bit
(CKP) = 0. This is done by writing to the synchronous serial
port control register (SSPCON). In this example, the input/output
Figure 46 is an example of a serial interface between the DAC and
the MC68HC11 microcontroller (Motorola). The serial peripheral
interface (SPI) on the MC68HC11 is configured for master mode
(MSTR) = 1, clock polarity bit (CPOL) = 0, and the clock phase
bit (CPHA) = 1. The SPI is configured by writing to the SPI control
register (SPCR); see the 68HC11 User Manual. SCK of the 68HC11
drives the SCLK of the DAC interface; the MOSI output drives
the serial data line (SDIN) of the DAC.
port RA1 is used to provide a
signal and enable the serial
SYNC
port of the DAC. This microcontroller transfers only eight bits
of data during each serial transfer operation; therefore, two
consecutive write operations are required. Figure 48 shows the
connection diagram.
The
signal is derived from a port line (PC7). When data
SYNC
PIC16C6x/7x1
AD54151
is transmitted to the AD5415, the
line is taken low (PC7).
SYNC
SCK/RC3
SDI/RC4
RA1
SCLK
Data appearing on the MOSI output is valid on the falling edge of
SCK. Serial data from the 68HC11 is transmitted in 8-bit bytes with
only eight falling clock edges occurring in the transmit cycle. Data
is transmitted MSB first. To load data to the DAC, leave PC7 low
after the first eight bits are transferred and perform a second serial
write operation to the DAC. PC7 is taken high at the end of this
procedure.
SDIN
SYNC
1
ADDITIONAL PINS OMITTED FOR CLARITY.
Figure 48. PIC16C6x/PIC16C7x to AD5415 Interface
Rev. F | Page 23 of 27
AD5415
Data Sheet
Components, such as clocks, that produce fast switching signals
must be shielded with digital ground to avoid radiating noise to
other parts of the board, and they must never be run near the
reference inputs.
PCB LAYOUT AND POWER SUPPLY DECOUPLING
In any circuit where accuracy is important, careful considera-
tion of the power supply and ground return layout ensures the
rated performance. The PCB on which the AD5415 is mounted
must be designed so that the analog and digital sections are
separated and confined to certain areas of the board. If the DAC
is in a system where multiple devices require an AGND to DGND
connection, the connection must be made at one point only. The
star ground point must be established as close as possible
to the device.
Avoid crossover of digital and analog signals. Traces on opposite
sides of the board must run at right angles to each other. This
reduces the effects of feedthrough on the board. A microstrip
technique is by far the best, but the use of the technique is not
always possible with a double-sided board. In this technique,
the component side of the board is dedicated to the ground
plane, and signal traces are placed on the soldered side.
The DAC must have ample supply bypassing of 10 µF in parallel
with 0.1 µF on the supply located as close as possible to the
package, ideally right up against the device. The 0.1 µF capacitor
must have low effective series resistance (ESR) and low effective
series inductance (ESI), like the common ceramic types of
capacitors that provide a low impedance path to ground at high
frequencies, to handle transient currents due to internal logic
switching. Low ESR 1 µF to 10 µF tantalum or electrolytic
capacitors must also be applied at the supplies to minimize
transient disturbance and filter out low frequency ripple.
It is good practice to use a compact, minimum lead length PCB
layout design. Leads to the input must be as short as possible to
minimize IR drops and stray inductance.
The PCB metal traces between VREF and RFB must also be
matched to minimize gain error. To maximize high frequency
performance, the I-to-V amplifier must be located as close as
possible to the device.
Rev. F | Page 24 of 27
Data Sheet
AD5415
OVERVIEW OF THE AD5424 TO AD5547 DEVICES
Table 13.
Part No.
AD5424
AD5426
AD5428
AD5429
AD5450
AD5432
AD5433
AD5439
AD5440
AD5451
AD5443
AD5444
AD5415
AD5405
AD5445
AD5447
AD5449
AD5452
AD5446
AD5453
AD5553
AD5556
AD5555
AD5557
AD5543
AD5546
AD5545
AD5547
Resolution
No. DACs
INL (LSB)
Interface
Parallel
Serial
Package1
RU-16, CP-20
RM-10
RU-20
Features
8
1
1
2
2
1
1
1
2
2
1
1
1
2
2
2
2
2
1
1
1
1
1
2
2
1
1
2
2
0.25
0.25
0.25
0.25
0.25
0.5
0.5
0.5
0.5
0.25
1
10 MHz BW, 17 ns CS pulse width
10 MHz BW, 50 MHz serial
8
8
Parallel
Serial
10 MHz BW, 17 ns CS pulse width
10 MHz BW, 50 MHz serial
8
RU-10
8
Serial
UJ-8
10 MHz BW, 50 MHz serial
10
10
10
10
10
12
12
12
12
12
12
12
12
14
14
14
14
14
14
16
16
16
16
Serial
RM-10
RU-20, CP-20
RU-16
10 MHz BW, 50 MHz serial
Parallel
Serial
10 MHz BW, 17 ns CS pulse width
10 MHz BW, 50 MHz serial
Parallel
Serial
RU-24
10 MHz BW, 17 ns CS pulse width
10 MHz BW, 50 MHz serial
UJ-8
Serial
RM-10
RM-8
10 MHz BW, 50 MHz serial
0.5
1
Serial
10 MHz BW, 50 MHz serial
Serial
RU-24
10 MHz BW, 50 MHz serial
1
Parallel
Parallel
Parallel
Serial
CP-40
10 MHz BW, 17 ns CS pulse width
10 MHz BW, 17 ns CS pulse width
10 MHz BW, 17 ns CS pulse width
10 MHz BW, 50 MHz serial
1
RU-20, CP-20
RU-24
1
1
RU-16
0.5
1
Serial
UJ-8, RM-8
RM-8
10 MHz BW, 50 MHz serial
Serial
10 MHz BW, 50 MHz serial
2
Serial
UJ-8, RM-8
RM-8
10 MHz BW, 50 MHz serial
1
Serial
4 MHz BW, 50 MHz serial clock
4 MHz BW, 20 ns WR pulse width
4 MHz BW, 50 MHz serial clock
4 MHz BW, 20 ns WR pulse width
4 MHz BW, 50 MHz serial clock
4 MHz BW, 20 ns WR pulse width
4 MHz BW, 50 MHz serial clock
4 MHz BW, 20 ns WR pulse width
1
Parallel
Serial
RU-28
1
RM-8
1
Parallel
Serial
RU-38
2
RM-8
2
Parallel
Serial
RU-28
2
RU-16
2
Parallel
RU-38
1 RU = TSSOP, CP = LFCSP, RM = MSOP, UJ = TSOT.
Rev. F | Page 25 of 27
AD5415
Data Sheet
OUTLINE DIMENSIONS
7.90
7.80
7.70
24
13
12
4.50
4.40
4.30
6.40 BSC
1
PIN 1
0.65
BSC
1.20
MAX
0.15
0.05
0.75
0.60
0.45
8°
0°
0.30
0.19
0.20
0.09
SEATING
PLANE
0.10 COPLANARITY
COMPLIANT TO JEDEC STANDARDS MO-153-AD
Figure 49. 24-Lead Thin Shrink Small Outline Package [TSSOP]
(RU-24)
Dimensions shown in millimeters
ORDERING GUIDE
Model1
Resolution
INL (LSB) Temperature Range
Package Description
Package Option
RU-24
AD5415YRUZ
12
12
12
1
1
1
−40°C to +125°C
−40°C to +125°C
−40°C to +125°C
24-Lead TSSOP
24-Lead TSSOP
24-Lead TSSOP
Evaluation Board
AD5415YRUZ-REEL
AD5415YRUZ-REEL7
EV-AD5415/49SDZ
RU-24
RU-24
1 Z = RoHS Compliant Part.
Rev. F | Page 26 of 27
Data Sheet
NOTES
AD5415
©2004–2015 Analog Devices, Inc. All rights reserved. Trademarks and
registered trademarks are the property of their respective owners.
D04461-0-12/15(F)
Rev. F | Page 27 of 27
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