AD585A [ADI]
High Speed, Precision Sample-and-Hold Amplifier; 高速，高精度采样保持放大器
| 型号： | AD585A |
| 厂家： | 
ADI |
| 描述： | High Speed, Precision Sample-and-Hold Amplifier |
| 文件： | 总6页 (文件大小：342K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
High Speed, Precision
Sample-and-Hold Amplifier
a
AD585
FEATURES
FUNCTIONAL BLOCK DIAGRAM
3.0 s Acquisition Time to ؎0.01% max
Low Droop Rate: 1.0 mV/ms max
Sample/Hold Offset Step: 3 mV max
Aperture Jitter: 0.5 ns
DIP
LCC/PLCC Package
Extended Temperature Range: –55؇C to +125؇C
Internal Hold Capacitor
Internal Application Resistors
؎12 V or ؎15 V Operation
Available in Surface Mount
APPLICATIONS
Data Acquisition Systems
Data Distribution Systems
Analog Delay & Storage
Peak Amplitude Measurements
MIL-STD-883 Compliant Versions Available
The AD585 is available in three performance grades. The JP
grade is specified for the 0°C to +70°C commercial temperature
range and packaged in a 20-pin PLCC. The AQ grade is speci-
fied for the –25°C to +85°C industrial temperature range and is
packaged in a 14-pin cerdip. The SQ and SE grades are speci-
fied for the –55°C to +125°C military temperature range and
are packaged in a 14-pin cerdip and 20-pin LCC.
PRODUCT DESCRIPTION
The AD585 is a complete monolithic sample-and-hold circuit
consisting of a high performance operational amplifier in series
with an ultralow leakage analog switch and a FET input inte-
grating amplifier. An internal holding capacitor and matched
applications resistors have been provided for high precision and
applications flexibility.
The performance of the AD585 makes it ideal for high speed
10- and 12-bit data acquisition systems, where fast acquisition
time, low sample-to-hold offset, and low droop are critical. The
AD585 can acquire a signal to ±0.01% in 3 µs maximum, and
then hold that signal with a maximum sample-to-hold offset of
3 mV and less than 1 mV/ms droop, using the on-chip hold
capacitor. If lower droop is required, it is possible to add a
larger external hold capacitor.
PRODUCT HIGHLIGHTS
1. The fast acquisition time (3 µs) and low aperture jitter
(0.5 ns) make it the first choice for very high speed data
acquisition systems.
2. The droop rate is only 1.0 mV/ms so that it may be used in
slower high accuracy systems without the loss of accuracy.
3. The low charge transfer of the analog switch keeps sample-to
hold offset below 3 mV with the on-chip 100 pF hold capaci-
tor, eliminating the trade-off between acquisition time and
S/H offset required with other SHAs.
The high speed analog switch used in the AD585 exhibits
aperture jitter of 0.5 ns, enabling the device to sample full scale
(20 V peak-to-peak) signals at frequencies up to 78 kHz with
12-bit precision.
4. The AD585 has internal pretrimmed application resistors for
applications versatility.
The AD585 can be used with any user-defined feedback net-
work to provide any desired gain in the sample mode. On-chip
precision thin-film resistors can be used to provide gains of +1,
–1, or +2. Output impedance in the hold mode is sufficiently
low to maintain an accurate output signal even when driving the
dynamic load presented by a successive-approximation A/D
converter. However, the output is protected against damage
from accidental short circuits.
5. The AD585 is complete with an internal hold capacitor for
ease of use. Capacitance can be added externally to reduce
the droop rate when long hold times and high accuracy are
required.
6. The AD585 is recommended for use with 10- and 12-bit
successive-approximation A/D converters such as AD573,
AD574A, AD674A, AD7572 and AD7672.
The control signal for the HOLD command can be either active
high or active low. The differential HOLD signal is compatible
with all logic families, if a suitable reference level is provided. An
on-chip TTL reference level is provided for TTL compatibility.
7. The AD585 is available in versions compliant with MIL-STD-
883. Refer to the Analog Devices Military Products Databook
or current AD585/883B data sheet for detailed specifications.
REV. A
Information furnished by Analog Devices is believed to be accurate and
reliable. However, no responsibility is assumed by Analog Devices for its
use, nor for any infringements of patents or other rights of third parties
which may result from its use. No license is granted by implication or
otherwise under any patent or patent rights of Analog Devices.
One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A.
Tel: 617/329-4700
Fax: 617/326-8703
(typical @ +25؇C and VS = ؎12 V or ؎15 V, and CH = Internal, A = +1,
AD585–SPECIFICATIONS HOLD active unless otherwise noted)
Model
AD585J
Typ
AD585A
Typ
AD585S
Typ
Min
Max
Min
Max
Min
Max
Units
SAMPLE/HOLD CHARACTERISTICS
Acquisition Time, 10 V Step to 0.01%
20 V Step to 0.01%
3
5
3
5
3
5
µs
µs
Aperture Time, 20 V p-p Input,
HOLD 0 V
Aperture Jitter, 20 V p-p Input,
35
35
35
ns
ns
HOLD 0 V
0.5
0.5
0.5
0.5
0.5
0.5
Settling Time, 20 V p-p Input,
HOLD 0 V, to 0.01%
Droop Rate
µs
mV/ms
1
1
1
Droop Rate TMIN to TMAX
Charge Transfer
Doubles Every 10°C
0.3
Double Every 10°C
0.3
Doubles Every 10°C
0.3
pC
Sample-to-Hold Offset
Feedthrough
20 V p-p, 10 kHz Input
TRANSFER CHARACTERISTICS1
Open Loop Gain
VOUT = 20 V p-p, RL = 2k
Application Resistor Mismatch
Common-Mode Rejection
VCM = ±10 V
–3
3
–3
80
3
–3
80
3
mV
0.5
0.5
0.5
mV
200,000
200,000
200,000
V/V
%
0.3
0.3
0.3
80
dB
Small Signal Gain Bandwidth
V
OUT = 100 mV p-p
2.0
160
10
2.0
160
10
2.0
160
10
MHz
kHz
V/µs
Full Power Bandwidth
VOUT = 20 V p-p
Slew Rate
V
OUT = 20 V p-p
Output Resistance (Sample Mode)
OUT = ±10 mA
I
0.05
0.05
0.05
Ω
Output Short Circuit Current
Output Short Circuit Duration
50
Indefinite
50
Indefinite
50
Indefinite
mA
ANALOG INPUT CHARACTERISTICS
Offset Voltage
Offset Voltage, TMIN to TMAX
Bias Current
Bias Current, TMIN to TMAX
Input Capacitance, f = 1 MHz
Input Resistance, Sample or Hold
20 V p-p Input, A = +1
5
6
2
5
2
3
2
5
2
3
mV
mV
nA
nA
pF
2
20
10
502
10
10
1012
1012
1012
Ω
DIGITAL INPUT CHARACTERISTICS
TTL Reference Output
Logic Input High Voltage
1.2
1.4
1.6
1.2
1.4
1.6
1.2
2.0
1.4
1.6
V
V
T
MIN to TMAX
2.0
2.0
Logic Input Low Voltage
TMIN to TMAX
Logic Input Current (Either Input)
0.8
50
0.8
50
0.7
50
V
µA
POWER SUPPLY CHARACTERISTICS
Operating Voltage Range
+5, –10.8
±18
+5, –10.8
±18
+5, –10.8
±18
V
Supply Current, RL = ∞
Power Supply Rejection, Sample Mode
6
70
10
6
70
10
6
70
10
mA
dB
TEMPERATURE RANGE
Specified Performance
0
+70
–25
+85
–55
+125
°C
PACKAGE OPTIONS3, 4
Cerdip (Q-14)
LCC (E-20A)
AD585AQ
AD585SQ
AD585SE
PLCC (P-20A)
AD585JP
NOTES
Specifications subject to change without notice.
1Maximum input signal is the minimum supply minus a headroom voltage of 2.5 V.
2Not tested at –55°C.
Specifications shown in boldface are tested on all production units at final electrical
test. Results from those tests are used to calculate outgoing quality levels.
All min and max specifications are guaranteed, although only those shown in
boldface are tested on all production units.
3E = Leadless Ceramic Chip Carrier; P = Plastic Leaded Chip Carrier; Q = Cerdip.
4For AD585/883B specifications, refer to Analog Devices Military Products Databook.
–2–
REV. A
AD585
ABSOLUTE MAXIMUM RATINGS
Supplies (+VS, –VS) . . . . . . . . . . . . . . . . . . . . . . . . . . . . .±18 V
Logic Inputs . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . ±VS
Analog Inputs . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . ±VS
RIN, RFB Pins . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . ±VS
Storage Temperature . . . . . . . . . . . . . . . . . . . –65°C to +150°C
Lead Temperature (Soldering) . . . . . . . . . . . . . . . . . . . 300°C
Output Short Circuit to Ground . . . . . . . . . . . . . . . . Indefinite
TTL Logic Reference Short
Circuit to Ground . . . . . . . . . . . . . . . . . . . . . . . . . Indefinite
Figure 2. Acquisition Time vs. Hold Capacitance
(10 V Step to 0.01%)
REV. A
–3–
AD585
SAMPLED DATA SYSTEMS
2–(N +1)
In sampled data systems there are a number of limiting factors
in digitizing high frequency signals accurately. Figure 9 shows
pictorially the sample-and-hold errors that are the limiting fac-
tors. In the following discussions of error sources the errors will
be divided into the following groups: 1. Sample-to-Hold Transi-
tion, 2. Hold Mode and 3. Hold-to-Sample Transition.
fMAX
=
π (Aperture Jitter)
For an application with a 10-bit A/D converter with a 10 V full
scale to a 1/2 LSB error maximum.
2–(10 +1)
π (0.5 × 10–9
fMAX
=
)
fMAX = 310.8 kHz.
For an application with a 12-bit A/D converter with a 10 V full
scale to a 1/2 LSB error maximum:
2–(12 +1)
π (0.5 × 10–9
fMAX
=
)
fMAX = 77.7 kHz.
Figure 11 shows the entire range of errors induced by aperture
jitter with respect to the input signal frequency.
Figure 9. Pictorial Showing Various S/H Characteristics
SAMPLE-TO-HOLD TRANSITION
The aperture delay time is the time required for the sample-and-
hold amplifier to switch from sample to hold. Since this is effec-
tively a constant then it may be tuned out. If however, the
aperture delay time is not accounted for then errors of the mag-
nitude as shown in Figure 10 will result.
Figure 11. Aperture Jitter Error vs. Frequency
Sample-to-hold offset is caused by the transfer of charge to the
holding capacitor via the gate capacitance of the switch when
switching into hold. Since the gate capacitance couples the
switch control voltage applied to the gate on to the hold capaci-
tor, the resulting sample-to-hold offset is a function of the logic
level .
Figure 10. Aperture Delay Error vs. Frequency
The logic inputs were designed for application flexibility and,
therefore, a wide range of logic thresholds. This was achieved by
using a differential input stage for HOLD and HOLD. Figure 1
shows the change in the sample-to-hold offset voltage based
upon an independently programmed reference voltage. Since
the input stage is a differential configuration, the offset voltage
is a function of the control voltage range around the pro-
grammed threshold voltage.
To eliminate the aperture delay as an error source the sample-
to-hold command may be advanced with respect to the input
signal .
Once the aperture delay time has been eliminated as an error
source then the aperture jitter which is the variation in aperture
delay time from sample-to-sample remains. The aperture jitter is
a true error source and must be considered. The aperture jitter
is a result of noise within the switching network which modu-
lates the phase of the hold command and is manifested in the
variations in the value of the analog input that has been held.
The aperture error which results from this jitter is directly re-
lated to the dV/dT of the analog input.
The sample-to-hold offset can be reduced by adding capacitance
to the internal 100 pF capacitor and by using HOLD instead of
HOLD. This may be easily accomplished by adding an external
capacitor between Pins 7 and 8. The sample-to-hold offset is
then governed by the relationship:
The error due to aperture jitter is easily calculated as shown be-
low. The error calculation takes into account the desired accu-
racy corresponding to the resolution of the N-bit A/D converter.
Charge pC
CH Total (pF )
(
)
S/H Offset (V ) =
–4–
REV. A
AD585
For the AD585 in particular it becomes:
0.3 pC
100 pF + C
HOLD-TO-SAMPLE TRANSITION
The Nyquist theorem states that a band-limited signal which is
sampled at a rate at least twice the maximum signal frequency
can be reconstructed without loss of information. This means
that a sampled data system must sample, convert and acquire
the next point at a rate at least twice the signal frequency. Thus
the maximum input frequency is equal to
S/H Offset (V ) =
(
)
EXT
The addition of an external hold capacitor also affects the acqui-
sition time of the AD585. The change in acquisition time with
respect to the CEXT is shown graphically in Figure 2.
1
fMAX
=
HOLD MODE
2 T
(
+TCONV +TAP
)
ACQ
In the hold mode there are two important specifications that
must be considered; feedthrough and the droop rate. Feedthrough
errors appear as an attenuated version of the input at the output
while in the hold mode. Hold-Mode feedthrough varies with fre-
quency, increasing at higher frequencies. Feedthrough is an im-
portant specification when a sample and hold follows an analog
multiplexer that switches among many different channels.
Where TACQ is the acquisition time of the sample-to-hold
amplifier, TAP is the maximum aperture time (small enough to
be ignored) and TCONV is the conversion time of the A/D
converter.
DATA ACQUISITION SYSTEMS
The fast acquisition time of the AD585 when used with a high
speed A/D converter allows accurate digitization of high fre-
quency signals and high throughput rates in multichannel data
acquisition systems. The AD585 can be used with a number of
different A/D converters to achieve high throughput rates. Fig-
ures 12 and 13 show the use of an AD585 with the AD578 and
AD574A.
Hold-mode droop rate is the change in output voltage per unit
of time while in the hold mode. Hold-mode droop originates as
leakage from the hold capacitor, of which the major leakage
current contributors are switch leakage current and bias current.
The rate of voltage change on the capacitor dV/dT is the ratio of
the total leakage current IL to the hold capacitance CH.
dVOUT
dT
IL (pA)
Droop Rate =
(Volts/Sec) =
C
H (pF)
For the AD585 in particular;
100 pA
100 pF +(CEXT
Droop Rate =
)
Additionally the leakage current doubles for every 10°C increase
in temperature above 25°C; therefore, the hold-mode droop rate
characteristic will also double in the same fashion. The hold-mode
droop rate can be traded-off with acquisition time to provide the
best combination of droop error and acquisition time. The tradeoff
is easily accomplished by varying the value of CEXT
.
Since a sample and hold is used typically in combination with
an A/D converter, then the total droop in the output voltage has
to be less than 1/2 LSB during the period of a conversion. The
maximum allowable signal change on the input of an A/D
converter is:
Figure 12. A/D Conversion System, 117.6 kHz Throughput
58.8 kHz max Signal Input
Full -Scale Voltage
∆V max =
2(N +1
)
Once the maximum ∆V is determined then the conversion time
of the A/D converter (TCONV) is required to calculate the maxi-
mum allowable dV/dT.
dV
dt
∆V max
TCONV
max =
dV max
dT
The maximum
as shown by the previous equation is
the limit not only at 25°C but at the maximum expected operat-
ing temperature range. Therefore, over the operating temperature
range the following criteria must be met (TOPERATION –25°C)
Figure 13. 12-Bit A/D Conversion System, 26.3 kHz
Throughput Rate, 13.1 kHz max Signal Input
= ∆T.
∆T °C
(
)
dV 25°C
dV max
dT
10°C
× 2
≤
dT
REV. A
–5–
AD585
LOGIC INPUT
ence between the voltage being measured and the voltage previ-
ously measured determines the fraction by which the
dielectric absorption figure is multiplied. It is impossible to
readily correct for this error source. The only solution is to use a
capacitor with dielectric absorption less than the maximum
tolerable error. Capacitor types such as polystyrene, polypropy-
lene or Teflon are recommended.
The sample-and-hold logic control was designed for versatile
logic interfacing. The HOLD and HOLD inputs may be used
with both low and high level CMOS, TTL and ECL logic sys-
tems. Logic threshold programmability was achieved by using a
differential amplifier as the input stage for the digital inputs. A
predictable logic threshold may be programmed by referencing
either HOLD or HOLD to the appropriate threshold voltage.
For example, if the internal 1.4 V reference is applied to HOLD
an input signal to HOLD between +1.8 V and +VS will place
the AD585 in the hold mode. The AD585 will go into the
sample mode for this case when the input is between –VS and
+1.0 V. The range of references which may be applied is from
(–VS +4 V) to (+VS –3 V).
GROUNDING
Many data-acquisition components have two or more ground
pins which are not connected together within the device. These
“grounds” are usually referred to as the Logic Power Return
Analog Common (Analog Power Return), and Analog Signal
Ground. These grounds must be tied together at one point,
usually at the system power-supply ground. Ideally, a single
solid ground would be desirable. However, since current flows
through the ground wires and etch stripes of the circuit cards,
and since these paths have resistance and inductance, hundreds
of millivolts can be generated between the system ground point
and the ground pin of the AD585. Separate ground returns
should be provided to minimize the current flow in the path
from sensitive points to the system ground point. In this way
supply currents and logic-gate return currents are not summed
into the same return path as analog signals where they would
cause measurement errors.
OPTIONAL CAPACITOR SELECTION
If an additional capacitor is going to be used in conjunction
with the internal 100 pF capacitor it must have a low dielectric
absorption. Dielectric absorption is just that; it is the charge
absorbed into the dielectric that is not immediately added to or
removed from the capacitor when rapidly charged or discharged.
The capacitor with dielectric absorption is modeled in Figure 14.
Figure 14. Capacitor Model with Dielectric Absorption
If the capacitor is charged slowly, CDA will eventually charge to
the same value as C. But unfortunately, good dielectrics have
very high resistances, so while CDA may be small, RX is large and
the time constant RX CDA typically runs into the millisecond
range. In fast charge, fast-discharge situations the effect of di-
electric absorption resembles “memory”. In a data acquisition
system where many channels with widely varying data are being
sampled the effect is to have an ever changing offset which ap-
pears as a very nonlinear sample-to-hold offset since the differ-
Figure 15. Basic Grounding Practice
OUTLINE DIMENSIONS
Dimensions shown in inches and (mm).
20-Terminal PLCC (P-20A)
20-Terminal LCC (E-20A)
14-Pin Cerdip (Q-14)
–6–
REV. A
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