AD7303BNZ [ADI]
2.7 V to 5.5 V, Serial Input, Dual Voltage Output 8-Bit DAC; 2.7 V至5.5 V ，串行输入，双路电压输出8位DAC
| 型号： | AD7303BNZ |
| 厂家： | 
ADI |
| 描述： | 2.7 V to 5.5 V, Serial Input, Dual Voltage Output 8-Bit DAC |
| 文件： | 总16页 (文件大小：292K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
+2.7 V to +5.5 V, Serial Input, Dual
Voltage Output 8-Bit DAC
a
AD7303
FUNCTIONAL BLOCK DIAGRAM
FEATURES
Two 8-Bit DACs in One Package
8-Pin DIP/SOIC and microSOIC Packages
+2.7 V to +5.5 V Operation
Internal & External Reference Capability
Individual DAC Power-Down Function
Three-Wire Serial Interface
QSPI™, SPI™ and Microwire™ Compatible
On-Chip Output Buffer
Rail-to-Rail Operation
AD7303
INPUT
REGISTER
DAC
REGISTER
I DAC A
I/V
I/V
V
A
B
OUT
OUT
DAC
REGISTER
INPUT
REGISTER
I DAC B
MUX
V
POWER ON
RESET
CONTROL (8)
DATA (8)
DIN
SCLK
SYNC
On-Chip Control Register
Low Power Operation: 2.3 mA @ 3.3 V
Full Power-Down to 1 A max, typically 80 nA
16-BIT SHIFT REGISTER
÷2
V
REF
GND
DD
APPLICATIONS
Portable Battery Powered Instruments
Digital Gain and Offset Adjustment
Programmable Voltage and Current Sources
Programmable Attenuators
PRODUCT HIGHLIGHTS
GENERAL DESCRIPTION
1. Low power, single supply operation. This part operates from
a single +2.7 V to +5.5 V supply and consumes typically
15 mW at 5.5 V, making it ideal for battery powered
applications.
The AD7303 is a dual, 8-bit voltage out DAC that operates
from a single +2.7 V to +5.5 V supply. Its on-chip precision out-
put buffers allow the DAC outputs to swing rail to rail. This de-
vice uses a versatile 3-wire serial interface that operates at clock
rates up to 30 MHz, and is compatible with QSPI, SPI, microwire
and digital signal processor interface standards. The serial input
register is sixteen bits wide; 8 bits act as data bits for the DACs,
and the remaining eight bits make up a control register.
2. The on-chip output buffer amplifiers allow the outputs of the
DACs to swing rail to rail with a settling time of typically 1.2 µs.
3. Internal or external reference capability.
4. High speed serial interface with clock rates up to 30 MHz.
The on-chip control register is used to address the relevant
DAC, to power down the complete device or an individual
DAC, to select internal or external reference and to provide a
synchronous loading facility for simultaneous update of the
DAC outputs with a software LDAC function.
5. Individual power-down of each DAC provided. When com-
pletely powered down, the DAC consumes typically 80 nA.
The low power consumption of this part makes it ideally suited
to portable battery operated equipment. The power consump-
tion is 7.5 mW max at 3 V, reducing to less than 3 µW in full
power-down mode.
The AD7303 is available in an 8-pin plastic dual in-line pack-
age, 8-lead SOIC and microSOIC packages.
QSPI and SPI are trademarks of Motorola.
Microwire is a trademark of National Semiconductor.
REV. 0
Information furnished by Analog Devices is believed to be accurate and
reliable. However, no responsibility is assumed by Analog Devices for its
use, nor for any infringements of patents or other rights of third parties
which may result from its use. No license is granted by implication or
otherwise under any patent or patent rights of Analog Devices.
One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A.
Tel: 617/329-4700
Fax: 617/326-8703
World Wide Web Site: http://www.analog.com
© Analog Devices, Inc., 1997
(VDD = +2.7 V to +5.5 V, Internal Reference; RL = 10 k⍀ to VDD and GND; CL = 100 pF
AD7303–SPECIFICATIONS to GND; all specifications TMIN to TMAX unless otherwise noted)
Parameter
B Versions1
Units
Conditions/Comments
STATIC PERFORMANCE
Resolution
8
Bits
Relative Accuracy
±1
±1
3
–0.5
+1
100
LSB max
LSB max
LSB max
LSB typ
% FSR typ
µV/°C typ
Note 2
Differential Nonlinearity
Zero-Code Error @ +25°C
Full-Scale Error
Guaranteed Monotonic
All Zeros Loaded to DAC Register
All Ones Loaded to DAC Register
Gain Error3
Zero-Code Temperature Coefficient
DAC REFERENCE INPUT
REFIN Input Range
1 to VDD/2
10
±1
V min to max
ΜΩ typ
% max
REFIN Input Impedance
Internal Voltage Reference Error 4
OUTPUT CHARACTERISTICS
Output Voltage Range
Output Voltage Settling Time
Slew Rate
Digital to Analog Glitch Impulse
Digital Feedthrough
Digital Crosstalk
Analog Crosstalk
DC Output Impedance
Short Circuit Current
Power Supply Rejection Ratio
0 to VDD
2
7.5
0.5
0.2
0.2
±0.2
40
14
0.0001
V min to max
µs max
Typically 1.2 µs
V/µs typ
nV-s typ
nV-s typ
nV-s typ
LSB typ
Ω typ
1 LSB Change Around Major Carry
mA typ
%/% max
∆ VDD = ±10%
LOGIC INPUTS
Input Current
±10
0.8
0.6
2.4
2.1
5
µA max
V max
V max
V min
V min
pF max
V
INL, Input Low Voltage
VDD = +5 V
V
DD = +3 V
VDD = +5 V
DD = +3 V
V
INH, Input High Voltage
V
Pin Capacitance
POWER REQUIREMENTS
VDD
2.7/5.5
V min/max
I
DD (Normal Mode)
Both DACs Active and Excluding Load Currents,
VIH = VDD, VIL = GND
V
DD = 3.3 V
@ +25°C
2.1
2.3
mA max
mA max
See Figure 8
TMIN – TMAX
V
DD = 5.5 V
@ +25°C
2.7
3.5
mA max
mA max
TMIN – TMAX
I
DD (Full Power-Down)
@ +25°C
80
1
nA typ
µA max
V
IH = VDD, VIL = GND
TMIN – TMAX
See Figure 19
NOTES
1Temperature ranges are as follows: B Version, –40°C to +105°C.
2Relative Accuracy is calculated using a reduced digital code range of 15 to 245.
3Gain Error is specified between Codes 15 and 245. The actual error at Code 15 is typically 3 LSB.
4Internal Voltage Reference Error = (Actual VREF – Ideal VREF/Ideal VREF) • 100. Ideal VREF = VDD/2, actual VREF = voltage on reference pin when internal reference
is selected.
Specifications subject to change without notice.
ORDERING GUIDE
Temperature
Range
Package
Options*
Model
AD7303BN
AD7303BR
AD7303BRM
–40°C to +105°C
–40°C to +105°C
–40°C to +105°C
N-8
SO-8
RM-8
*N = Plastic DIP; R = SOIC; RM = microSOIC.
–2–
REV. 0
AD7303
(VDD = +2.7 V to +5.5 V; GND = 0 V; Reference = Internal VDD/2 Reference; all specifications
TMIN to TMAX unless otherwise noted)
TIMING CHARACTERISTICS1, 2
Parameter
Limit at TMIN, TMAX (B Version)
Units
Conditions/Comments
t1
t2
t3
t4
t5
t6
t7
t8
33
13
13
5
ns min
ns min
ns min
ns min
ns min
ns min
ns min
ns min
SCLK Cycle Time
SCLK High Time
SCLK Low Time
SYNC Setup Time
Data Setup Time
Data Hold Time
SYNC Hold Time
Minimum SYNC High Time
5
4.5
4.5
33
NOTES
1Sample tested at +25°C to ensure compliance. All input signals are specified with tr = tf = 5 ns (10% to 90% of VDD) and timed from a voltage level of (VIL + VIH)/2,
tr and tf should not exceed 1 µs on any input.
2See Figures 1 and 2.
t1
SCLK (I)
t2
t3
t7
t4
t8
t4
SYNC (I)
t5
t6
DB15
DIN (I)
DB0
Figure 1. Timing Diagram for Continuous 16-Bit Write
t1
SCLK (I)
t3
t2
t7
t8
t4
SYNC (I)
t5
t5
t6
t6
DB15
DB8
DB7
DB0
DIN (I)
Figure 2. Timing Diagram for 2 × 8-Bit Writes
REV. 0
–3–
AD7303
ABSOLUTE MAXIMUM RATINGS*
(TA = +25°C unless otherwise noted)
SOIC Package, Power Dissipation . . . . . . . . . . . . . . . 450 mW
θJA Thermal Impedance . . . . . . . . . . . . . . . . . . . . . 157°C/W
Lead Temperature, Soldering
Vapor Phase (60 sec) . . . . . . . . . . . . . . . . . . . . . . +215°C
Infrared (15 sec) . . . . . . . . . . . . . . . . . . . . . . . . . . +220°C
MicroSOIC Package, Power Dissipation . . . . . . . . . . 450 mW
θJA Thermal Impedance . . . . . . . . . . . . . . . . . . . . . 206°C/W
Lead Temperature, Soldering
VDD to GND . . . . . . . . . . . . . . . . . . . . . . . . . . –0.3 V to +7 V
Reference Input Voltage to GND . . . . –0.3 V to VDD + 0.3 V
Digital Input Voltage to GND . . . . . . . –0.3 V to VDD + 0.3 V
V
OUT A, VOUT B to GND . . . . . . . . . . . –0.3 V to VDD + 0.3 V
Operating Temperature Range
Commercial (B Version) . . . . . . . . . . . . . –40°C to +105°C
Storage Temperature Range . . . . . . . . . . . . –65°C to +150°C
Junction Temperature . . . . . . . . . . . . . . . . . . . . . . . . . +150°C
Plastic DIP Package, Power Dissipation . . . . . . . . . . 800 mW
θJA Thermal Impedance . . . . . . . . . . . . . . . . . . . . . 117°C/W
Lead Temperature (Soldering, 10 sec) . . . . . . . . . . . +260°C
Vapor Phase (60 sec) . . . . . . . . . . . . . . . . . . . . . . +215°C
Infrared (15 sec) . . . . . . . . . . . . . . . . . . . . . . . . . . +220°C
*Stresses above those listed under “Absolute Maximum Ratings” may cause
permanent damage to the device. This is a stress rating only; functional operation
of the device at these or any other conditions above those listed in the operational
sections of this specification is not implied. Exposure to absolute maximum rating
conditions for extended periods may affect device reliability.
CAUTION
ESD (electrostatic discharge) sensitive device. Electrostatic charges as high as 4000 V readily
accumulate on the human body and test equipment and can discharge without detection.
Although the AD7303 features proprietary ESD protection circuitry, permanent damage may
occur on devices subjected to high energy electrostatic discharges. Therefore, proper ESD
precautions are recommended to avoid performance degradation or loss of functionality.
WARNING!
ESD SENSITIVE DEVICE
PIN CONFIGURATIONS
(DIP, SOIC and microSOIC)
V
B
V
A
1
2
3
4
8
7
6
5
OUT
OUT
V
SYNC
DIN
DD
GND
REF
AD7303
TOP VIEW
(Not to Scale)
SCLK
PIN FUNCTION DESCRIPTIONS
Pin
No. Mnemonic
Function
Analog Output Voltage from DAC A. The output amplifier swings rail to rail on its output.
1
2
3
4
VOUT A
VDD
Power Supply Input. These parts can be operated from +2.7 V to +5.5 V and should be decoupled to GND.
Ground reference point for all circuitry on the part.
GND
REF
External Reference Input. This can be used as the reference for both DACs, and is selected by setting the
INT/EXT bit in the control register to a logic one. The range on this reference input is 1 V to VDD/2. When
the internal reference is selected, this voltage will appear as an output for decoupling purposes at the REF Pin.
When using the internal reference, external voltages should not be connected to the REF Pin, see Figure 21.
5
6
7
SCLK
DIN
Serial Clock. Logic Input. Data is clocked into the input shift register on the rising edge of the serial clock
input. Data can be transferred at rates up to 30 MHz.
Serial Data Input. This device has a 16-bit shift register, 8 bits for data and 8 bits for control. Data is clocked
into the register on the rising edge of the clock input.
SYNC
Level Triggered Control Input (active low). This is the frame synchronization signal for the input data. When
SYNC goes low, it enables the input shift register and data is transferred in on the rising edges of the following
clocks. The rising edge of the SYNC causes the relevant registers to be updated.
8
VOUT
B
Analog output voltage from DAC B. The output amplifier swings rail to rail on its output.
–4–
REV. 0
AD7303
DIGITAL-TO-ANALOG GLITCH IMPULSE
TERMINOLOGY
Digital-to-analog glitch impulse is the impulse injected into the
analog output when the digital inputs change state with the
DAC selected and the software LDAC used to update the DAC.
It is normally specified as the area of the glitch in nV-s and is
measured when the digital input code is changed by 1 LSB at
the major carry transition.
INTEGRAL NONLINEARITY
For the DACs, relative accuracy or endpoint nonlinearity is a
measure of the maximum deviation, in LSBs, from a straight
line passing through the endpoints of the DAC transfer func-
tion. A graphical representation of the transfer curve is shown
in Figure 15.
DIGITAL FEEDTHROUGH
DIFFERENTIAL NONLINEARITY
Digital feedthrough is a measure of the impulse injected into the
analog output of a DAC from the digital inputs of the same
DAC, but is measured when the DAC is not updated. It is
specified in nV-s and measured with a full-scale code change on
the data bus, i.e., from all 0s to all 1s and vice versa.
Differential nonlinearity is the difference between the measured
change and the ideal 1 LSB change of any two adjacent codes. A
specified differential nonlinearity of ±1 LSB maximum ensures
monotonicity.
ZERO CODE ERROR
DIGITAL CROSSTALK
Zero code error is the measured output voltage from VOUT of
either DAC when zero code (all zeros) is loaded to the DAC
latch. It is due to a combination of the offset errors in the DAC
and output amplifier. Zero-scale error is expressed in LSBs.
Digital crosstalk is the glitch impulse transferred to the output
of one converter due to a digital code change to another DAC.
It is specified in nV-s.
GAIN ERROR
ANALOG CROSSTALK
This is a measure of the span error of the DAC. It is the devia-
tion in slope of the DAC transfer characteristic from ideal
expressed as a percent of the full-scale value. Gain error is calcu-
lated between Codes 15 and 245.
Analog crosstalk is a change in output of any DAC in response
to a change in the output of the other DAC. It is measured in
LSBs.
POWER SUPPLY REJECTION RATIO (PSRR)
FULL-SCALE ERROR
This specification indicates how the output of the DAC is
affected by changes in the power supply voltage. Power supply
rejection ratio is quoted in terms of % change in output per %
of change in VDD for full-scale output of the DAC. VDD is varied
± 10%. This specification applies to an external reference only
because the output voltage will track the VDD voltage when in-
ternal reference is selected.
Full-Scale Error is a measure of the output error when the DAC
latch is loaded with FF Hex. Full-scale error includes the offset
error.
REV. 0
–5–
AD7303–Typical Performance Characteristics
3.5
3.25
3
800
720
640
560
480
400
320
249
160
80
5
4.92
4.84
4.76
4.68
4.6
V
= +5V AND +3V
DD
INTERNAL REFERENCE
= 25؇C
T
A
DAC LOADED WITH 00HEX
2.75
2.5
2.25
2
V
= +3V
DD
4.52
4.44
4.36
4.28
4.2
INTERNAL REFERENCE
DAC REGISTER LOADED WITH FFHEX
1.75
1.5
1.25
1
T = 25°C
V
= +5V
A
DD
INTERNAL REFERENCE
DAC REGISTER LOADED WITH FFHEX
T
= 25°C
A
0
0
1
2
3
4
5
6
7
8
0
2
4
6
8
0
2
4
6
8
SOURCE CURRENT – mA
SINK CURRENT – mA
SOURCE CURRENT – mA
Figure 5. Output Source Current
Capability with VDD = 3 V
Figure 3. Output Sink Current Capa-
bility with VDD = 3 V and VDD = 5 V
Figure 4. Output Source Current
Capability with VDD = 5 V
5.5
0.5
5
V
= +5V
DD
= 25؇C
0.45
0.4
5
T
A
4.5
4
LOGIC INPUTS = V OR V
IH IL
INTERNAL REFERENCE
4.5
4
T
= 25°C
A
0.35
0.3
INTERNAL REFERENCE
= +5V
LOGIC INPUTS = V OR V
IH IL
INL ERROR
V
DD
3.5
3
0.25
0.2
3.5
3
0.15
0.1
DNL ERROR
2.5
2
LOGIC INPUTS = V OR GND
DD
2.5
2
0.05
LOGIC INPUTS = V OR GND
DD
1.5
2.5
0
1
1.2 1.4 1.6 1.8
2
2.2 2.4 2.6 2.8
3
3.5
4
4.5
5
5.5
–60 –40 –20
0
20 40 60 80 100 120 140
REFERENCE VOLTAGE – Volts
V
– Volts
TEMPERATURE – ؇C
DD
Figure 6. Relative Accuracy vs.
External Reference
Figure 8. Supply Current vs.
Supply Voltage
Figure 7. Supply Current vs.
Temperature
10
5
POWER UP TIME
V
= +5V
DD
INTERNAL REFERENCE
BOTH DACS IN POWER DOWN INITIALLY
T
0
V
= +3V
SYNC
DD
1
2
INTERNAL VOLTAGE REFERENCE
FULL SCALE CODE CHANGE 00H-FFH
–5
–10
–15
SYNC
T
= 25°C
2
1
A
V
= +5V
DD
V
OUT
–20
–25
–30
–35
–40
EXTERNAL SINE WAVE REFERENCE
DAC REGISTER LOADED WITH FFHEX
V
T
= 25°C
OUT
A
V
OUT
3
1
10
100
1000
10000
CH1 = 2V/div, CH2 = 5V/div,
TIME BASE = 2µs/div
FREQUENCY – kHz
CH1 5V, CH2 1V, CH3 20mV
TIME BASE = 200ns/div
Figure 11. Exiting Power-Down (Full
Power-Down)
Figure 10. Full-Scale Settling Time
Figure 9. Large Scale Signal
Frequency Response
–6–
REV. 0
AD7303
7
6
V
= +5V
DD
INTERNAL REFERENCE
= 25؇C
V
= +5V
T
A
SYNC
DD
T
INTERNAL VOLTAGE
REFERENCE
10 LSB STEP CHANGE
1
5
4
3
2
1
0
DAC A = NORMAL OPERATION
DAC B INITIALLY IN POWER
DOWN
←
SYNC
2
1
T
A
= 25؇C
V
= +5V
DD
V
OUT
DAC B EXITING
POWER DOWN
V
B
OUT
V
= +3V
DD
2
CH1 5.00V, CH2 50.0mV, M 250ns
CH1 2V, CH2 5V, M 500ns
0
0.5
1
1.5
2
2.5
3
3.5
4
4.5
5
Figure 14. Small Scale Settling
Time
Figure 12. Exiting Power-Down
(Partial Power-Down)
Figure 13. Supply Current vs.
Logic Input Voltage
0.5
0.4
0.3
0.2
0.1
0.5
0.5
V
= +5V
DD
0.4
0.3
0.2
0.1
0
0.4
INTERNAL REFERENCE
5kΩ 100pF LOAD
LIMITED CODE RANGE (10-245)
0.3
0.2
0.1
0
T
= 25°C
A
DAC A
V
= +5V
DD
V
= +5V
INTERNAL REFERENCE
DD
INTERNAL REFERENCE
0
–0.1
–0.2
–0.3
–0.4
–0.5
–0.1
–0.2
–0.3
–0.4
–0.5
–0.1
–0.2
DAC B
–0.3
–0.4
–0.5
–60 –40 –20
0
20 40 60 80 100 120 140
–60 –40 –20
0
20 40 60 80 100 120 140
0
32
64 96 128 160 192 224 255
Input Code (10 to 245)
TEMPERATURE – ؇C
TEMPERATURE – ؇C
Figure 17. Typical DNL vs.
Temperature
Figure 16. Typical INL vs.
Temperature
Figure 15. Integral Linearity Plot
500
400
1.0
0.8
V
V
= +5.5V
DD
AND V = 0V OR V
IL
IH DD
V
= +5V
DD
300
200
0.6
0.4
100
0
0.2
0
–50 –25
0
25
50
75 100 125 150
TEMPERATURE – ؇C
–60 –40 –20
0
20 40 60 80 100 120 140
TEMPERATURE – ؇C
Figure 19. Power-Down Current vs.
Temperature
Figure 18. Typical Internal Reference
Error vs. Temperature
REV. 0
–7–
AD7303
GENERAL DESCRIPTION
D/A Section
reference appears at the reference pin as an output voltage for
decoupling purposes. When using the internal reference, external
references should not be connected to the REF pin. If external ref-
erence is selected, both switches are open and the externally
applied voltage to the REF pin is applied to the reference amplifier.
The AD7303 is a dual 8-bit voltage output digital-to-analog
converter. The architecture consists of a reference amplifier and
a current source DAC, followed by a current-to-voltage con-
verter capable of generating rail-to-rail voltages on the output of
the DAC. Figure 20 shows a block diagram of the basic DAC
architecture.
Decoupling capacitors applied to the REF pin decouple both
the internal reference and external reference. In noisy environ-
ments it is recommended that a 0.1 µF capacitor be connected
to the REF pin to provide added decoupling even when the in-
ternal reference is selected.
V
DD
AD7303
REFERENCE
AMPLIFIER
11.7kΩ
Analog Outputs
30kΩ
CURRENT
DAC
The AD7303 contains two independent voltage output DACs
with 8-bit resolution and rail-to-rail operation. The output buffer
provides a gain of two at the output. Figures 3 to 5 show the sink
and source capabilities of the output amplifier. The slew rate of the
output amplifier is typically 8 V/µs and has a full-scale settling to 8
bits with a 100 pF capacitive load in typically 1.2 µs.
REF
V
O
A/B
11.7kΩ
OUTPUT
AMPLIFIER
30kΩ
The input coding to the DAC is straight binary. Table I shows
the binary transfer function for the AD7303. Figure 22 shows
the DAC transfer function for binary coding. Any DAC output
voltage can ideally be expressed as:
Figure 20. DAC Architecture
Both DAC A and DAC B outputs are internally buffered and
these output buffer amplifiers have rail-to-rail output character-
istics. The output amplifier is capable of driving a load of 10 kΩ
to both VDD and ground and 100 pF to ground. The reference
selection for the DAC can be either internally generated from
V
OUT = 2 × VREF (N/256)
where:
V
DD or externally applied through the REF pin. Reference
N
is the decimal equivalent of the binary input code.
selection is via a bit in the control register. The range on the
external reference input is from 1.0 V to VDD/2. The output
voltage from either DAC is given by:
N ranges from 0 to 255.
VREF is the voltage applied to the external REF pin when
the external reference is selected and is VDD/2 if the
internal reference is used.
VO A/B = 2 × VREF × (N/256)
where:
VREF is the voltage applied to the external REF pin or
Table I. Binary Code Table for AD7303 DAC
Digital Input
VDD/2 when the internal reference is selected.
MSB . . . LSB
Analog Output
N
is the decimal equivalent of the code loaded to the DAC
register and ranges from 0 to 255.
1111 1111
1111 1110
1000 0001
1000 0000
0111 1111
0000 0001
0000 0000
2 × 255/256 × VREF V
2 × 254/256 × VREF V
2 × 129/256 × VREF V
Reference
The AD7303 has the facility to use either an external reference
applied through the REF pin or an internal reference generated
from VDD. Figure 21 shows the reference input arrangement
where the internal VDD/2 has been selected.
VREF V
2 × 127/256 × VREF V
2 × VREF/256 V
0 V
AD7303
V
DD
2.V
REF
30kΩ
INT/EXT
REF
0.1µF
REFERENCE
AMPLIFIER
V
REF
30kΩ
Figure 21. Reference Input
0
When the internal reference is selected during the write to the
DAC, both switches are closed and VDD/2 is generated and
applied to the reference amplifier. This internal VDD/2 reference
appears at the reference pin as an output voltage for decoupling
purposes. When using the internal reference, external references
should not be connected to the REF Pin. This internal VDD/2
00
01
7F 80 81
FE
FF
DAC INPUT
CODE
Figure 22. DAC Transfer Function
–8–
REV. 0
AD7303
SERIAL INTERFACE
grammed to transfer data in 16-bit words. After clocking all six-
teen bits to the shift register, the rising edge of SYNC executes
the programmed function. The DACs are double buffered
which allows their outputs to be simultaneously updated.
The AD7303 contains a versatile 3-wire serial interface that is
compatible with SPI, QSPI and Microwire interface stan-
dards as well as a host of digital signal processors. An active
low SYNC enables the shift register to receive data from the
serial data input DIN. Data is clocked into the shift register on
the rising edge of the serial clock. The serial clock frequency
can be as high as 30 MHz. This shift register is 16 bits wide as
shown in Figures 23 and 24. The first eight bits are control bits
and the second eight bits are data bits for the DACs. Each
transfer must consist of a 16-bit transfer. Data is sent MSB first
and can be transmitted in one 16-bit write or two 8-bit writes.
SPI and Microwire interfaces output data in 8-bit bytes and
thus require two 8-bit transfers. In this case the SYNC input to
the DAC should remain low until all sixteen bits have been
transferred to the shift register. QSPI interfaces can be pro-
INPUT SHIFT REGISTER DESCRIPTION
The input shift register is 16 bits wide. The first eight bits con-
sist of control bits and the last eight bits are data bits. Figure 23
shows a block diagram of the logic interface on the AD7303
DAC. The seven bits in the control word are taken from the in-
put shift register to a latch sequencer that decodes this data and
provides output signals that control the data transfers to the in-
put and data registers of the selected DAC, as well as output
updating and various power-down features associated with the
control section. A description of all bits contained in the input
shift register is given below.
INT/EXT
X
MSB
DAC A POWER-DOWN
SYNC
DAC A BIAS
DAC B BIAS
DAC B POWER-DOWN
BANDGAP
BIAS GEN
LATCH
SEQUENCER
BANDGAP POWER-DOWN
LDAC
PDB
PDA
A/B
7
REF
SELECTOR
LATCH & CLK
DRIVERS
INT
16
REF
REFERENCE
CURRENT
SWITCH
RESISTOR
SWITCH
CR1
CR0
DB7
DB6
DB5
DB4
DB3
DB2
DB1
DB0
CLOCK BUS
30
8
30
8
INPUT
REGISTER
DAC
8 TO 32
DAC A
V
OUT
A
REGISTER
DECODER
8
30
8
30
8
INPUT
REGISTER
DAC
8 TO 32
DAC B
V
OUT
B
REGISTER
DECODER
LSB
SYNC
SCLK
DIN
Figure 23. Logic Interface on the AD7303
REV. 0
–9–
AD7303
DB15 (MSB)
DB0 (LSB)
DB1 DB0
X
LDAC PDB
PBA
CR1
CR0
DB7
DB6
DB5 DB4
DB3
DB2
INT/EXT
A/B
|––––––––––––––––––––––––– Control Bits –––––––––––––––––––––––––|––––––––––––––––––––––––– Data Bits –––––––––––––––––––––––––|
Figure 24. Input Shift Register Contents
Bit Location
Mnemonic
Description
DB15
DB14
DB13
DB12
DB11
DB10
DB9
INT/EXT
X
LDAC
PDB
PDA
A/B
CR1
CR0
Data
Selects between internal and external reference.
Uncommitted bit.
Load DAC bit for synchronous update of DAC outputs.
Power-down DAC B.
Power-down DAC A.
Address bit to select either DAC A or DAC B.
Control Bit 1 used in conjunction with CR0 to implement the various data loading functions.
Control Bit 0 used in conjunction with CR1 to implement the various data loading functions.
These bits contain the data used to update the output of the DACs. DB7 is the MSB and
DB0 the LSB of the 8-bit data word.
DB8
DB7–DB0
CONTROL BITS
LDAC
A/B
CR1
CR0
Function Implemented
0
0
0
0
0
0
0
1
X
0
1
0
1
0
1
0
0
0
0
1
1
1
1
X
0
1
1
0
0
1
1
X
Both DAC registers loaded from shift register.
Update DAC A input register from shift register.
Update DAC B input register from shift register.
Update DAC A DAC register from input register.
Update DAC B DAC register from input register.
Update DAC A DAC register from shift register.
Update DAC B DAC register from shift register.
Load DAC A input register from shift register and update
both DAC A and DAC B DAC registers.
1
1
X
X
Load DAC B input register from shift register and update
both DAC A and DAC B DAC registers outputs.
INT/EXT
Function
0
1
Internal VDD/2 reference selected.
External reference selected; this external reference is applied at the REF pin and ranges from
1 V to VDD/2.
PDA
PDB
Function
0
0
1
1
0
1
0
1
Both DACs active.
DAC A active and DAC B in power-down mode.
DAC A in power-down mode and DAC B active.
Both DACs powered down.
–10–
REV. 0
AD7303
POWER-ON RESET
AD7303 to 68HC11/68L11 Interface
The AD7303 has a power-on reset circuit designed to allow output
stability during power-up. This circuit holds the DACs in a reset
state until a write takes place to the DAC. In the reset state all zeros
are latched into the input registers of each DAC, and the DAC reg-
isters are in transparent mode. Thus the output of both DACs are
held at ground potential until a write takes place to the DAC.
Figure 27 shows a serial interface between the AD7303 and the
68HC11/68L11 microcontroller. SCK of the 68HC11/68L11
drives the CLKIN of the AD7303, while the MOSI output
drives the serial data line of the DAC. The SYNC signal is
derived from a port line (PC7). The setup conditions for cor-
rect operation of this interface are as follows: the 68HC11/
68L11 should be configured so that its CPOL bit is a 0 and its
CPHA bit is a 0. When data is being transmitted to the DAC,
the SYNC line is taken low (PC7). When the 68HC11/68L11 is
configured as above, data appearing on the MOSI output is
valid on the rising edge of SCK. Serial data from the 68HC11/
68L11 is transmitted in 8-bit bytes with only eight falling clock
edges occurring in the transmit cycle. Data is transmitted MSB
first. In order to load data to the AD7303, PC7 is left low after
the first eight bits are transferred, and a second serial write op-
eration is performed to the DAC and PC7 is taken high at the
end of this procedure.
POWER-DOWN FEATURES
Two bits in the control section of the 16-bit input word are used to
put the AD7303 into low power mode. DAC A and DAC B can be
powered down separately. When both DACs are powered down,
the current consumption of the device is reduced to less than 1 µA,
making the device suitable for use in portable battery powered
equipment. The reference bias servo loop, the output amplifiers
and associated linear circuitry are all shut down when the power-
down is activated. The output sees a load of approximately 23 kΩ
to GND when in power-down mode as shown in Figure 25. The
contents of the data registers are unaffected when in power-down
mode. The time to exit power-down is determined by the nature of
the power-down, if the device is fully powered down the bias gen-
erator is also powered down and the device takes typically 13 µs to
exit power-down mode. If the device is only partially powered
down, i.e., only one channel powered down, in this case the bias
generator is active and the time required for the power-down chan-
nel to exit this mode is typically 1.6 µs. See Figures 11 and 12.
68HC11/68L11*
AD7303*
SYNC
PC7
SCK
SCLK
DIN
MOSI
*ADDITIONAL PINS OMITTED FOR CLARITY
V
DD
11.7kΩ
Figure 27. AD7303 to 68HC11/68L11 Interface
AD7303 to 80C51/80L51 Interface
I
DAC
V
A/B
Figure 28 shows a serial interface between the AD7303 and the
80C51/80L51 microcontroller. The setup for the interface is as
follows: TXD of the 80C51/80L51 drives SCLK of the AD7303,
while RXD drives the serial data line of the part. The SYNC
signal is again derived from a bit programmable pin on the port.
In this case port line P3.3 is used. When data is to be transmit-
ted to the AD7303, P3.3 is taken low. The 80C51/80L51 trans-
mits data only in 8-bit bytes; thus only eight falling clock edges
occur in the transmit cycle. To load data to the DAC, P3.3 is
left low after the first eight bits are transmitted, and a second
write cycle is initiated to transmit the second byte of data. P3.3
is taken high following the completion of this cycle. The 80C51/
80L51 outputs the serial data in a format which has the LSB
first. The AD7303 requires its data with the MSB as the first bit
received. The 80C51/80L51 transmit routine should take this
into account.
O
11.7kΩ
V
REF
Figure 25. Output Stage During Power-Down
MICROPROCESSOR INTERFACING
AD7303 to ADSP-2101/ADSP-2103 Interface
Figure 26 shows a serial interface between the AD7303 and the
ADSP-2101/ADSP-2103. The ADSP-2101/ADSP-2103 should
be set up to operate in the SPORT Transmit Alternate Framing
Mode. The ADSP-2101/ADSP-2103 SPORT is programmed
through the SPORT control register and should be configured
as follows: Internal Clock Operation, Active Low Framing,
16-Bit Word Length. Transmission is initiated by writing a word
to the Tx register after the SPORT has been enabled. The data
is clocked out on each falling edge of the serial clock and clocked
into the AD7303 on the rising edge of the SCLK.
80C51/80L51*
AD7303*
SYNC
P3.3
TXD
RXD
SCLK
SDIN
ADSP-2101/
AD7303*
ADSP-2103*
SYNC
DIN
TFS
DT
*ADDITIONAL PINS OMITTED FOR CLARITY
Figure 28. AD7303 to 80C51/80L51 Interface
SCLK
SCLK
*ADDITIONAL PINS OMITTED FOR CLARITY
Figure 26. AD7303 to ADSP-2101/ADSP-2103 Interface
REV. 0
–11–
AD7303
AD7303 to Microwire Interface
Bipolar Operation Using the AD7303
Figure 29 shows an interface between the AD7303 and any
microwire compatible device. Serial data is shifted out on the
falling edge of the serial clock and is clocked into the AD7303
on the rising edge of the SK.
The AD7303 has been designed for single supply operation, but
bipolar operation is achievable using the circuit shown in Figure
31. The circuit shown has been configured to achieve an output
voltage range of –5 V < VO < +5 V. Rail-to-rail operation at the
amplifier output is achievable using an AD820 or OP295 as the
output amplifier.
MICROWIRE*
AD7303*
V
DD
= +5V
R4
20kΩ
SYNC
CS
SK
SCLK
DIN
0.1µF
10µF
+5V
–5V
R3
10kΩ
SO
V
±5V
IN
*ADDITIONAL PINS OMITTED FOR CLARITY
V
DD
EXT
REF
GND
V
OUT
REF
Figure 29. AD7303 to Microwire Interface
APPLICATIONS
0.1µF
AD7303
R1
10kΩ
V A
OUT
SCLK
DIN
R2
AD780/ REF192
WITH V = +5V
DD
Typical Application Circuit
20kΩ
SYNC
Figure 30 shows a typical setup for the AD7303 when using an
external reference. The reference range for the AD7303 is from
1 V to VDD/2 V. Higher values of reference can be incorporated
but will saturate the output at both the top and bottom end of
the transfer function. From input to output on the AD7303
there is a gain of two. Suitable references for 5 V operation are
the AD780 and REF192. For 3 V operation, a suitable external
reference would be the AD589, a 1.23 V bandgap reference.
OR
GND
AD589 WITH V = +3V
DD
SERIAL
INTERFACE
Figure 31. Bipolar Operation Using the AD7303
The output voltage for any input code can be calculated as
follows:
VO = [(1+R4/R3)*(R2/(R1+R2)*(2*VREF*D/256)] – R4*VREF/R3
V
DD
= +3V TO +5V
where
D is the decimal equivalent of the code loaded to the DAC
0.1µF
10µF
and
V
REF is the reference voltage input.
With VREF = 2.5 V, R1 = R3 = 10 kΩ and R2 = R4 = 20K and
DD = 5 V.
V
IN
V
DD
EXT
REF
V
REF
OUT
V
A
OUT
0.1µF
V
GND
AD7303
V
OUT = (10 × D/256) – 5
SCLK
DIN
Opto-Isolated Interface for Process Control Applications
The AD7303 has a versatile 3-wire serial interface making it
ideal for generating accurate voltages in process control and
industrial applications. Due to noise, safety requirements or dis-
tance, it may be necessary to isolate the AD7303 from the con-
troller. This can easily be achieved by using opto-isolators,
which will provide isolation in excess of 3 kV. The serial loading
structure of the AD7303 makes it ideally suited for use in opto-
isolated applications. Figure 32 shows an opto-isolated interface
to the AD7303 where DIN, SCLK and SYNC are driven from
opto-couplers. In this application the reference for the AD7303
is the internal VDD/2 reference. It is being decoupled at the REF
pin with a 0.1 µF ceramic capacitor for noise reduction purposes.
V
OUT
B
AD780/ REF192
WITH V = +5V
DD
SYNC
GND
OR
AD589 WITH V = +3V
DD
SERIAL
INTERFACE
Figure 30. AD7303 Using External Reference
The AD7303 can also be used with its own internally derived
DD/2 reference. Reference selection is through the INT/EXT
V
bit of the 16-bit input word. The internal reference, when
selected, is also provided as an output at the REF pin and can
be decoupled at this point with a 0.1 µF capacitor for noise
reduction purposes. AC references can also be applied as exter-
nal references to the AD7303. The AD7303 has limited multi-
plying capability, and a multiplying bandwidth of up to 10 kHz
is achievable.
–12–
REV. 0
AD7303
AD7303 as a Digitally Programmable Window Detector
A digitally programmable upper/lower limit detector using the
two DACs in the AD7303 is shown in Figure 34. The upper
and lower limits for the test are loaded to DACs A and B which,
in turn, set the limits on the CMP04. If a signal at the VIN input
is not within the programmed window, a led will indicate the fail
condition.
+5V
REGULATOR
0.1µF
10µF
POWER
V
DD
10kΩ
V
DD
SCLK
SCLK
REF
0.1µF
+5V
V
AD7303
DD
0.1µF
REF
10µF
1kΩ
1kΩ
V
IN
10kΩ
PASS
FAIL
V
V
A
B
SYNC
OUT
SYNC
V
DD
0.1µF
V
A
OUT
OUT
V
DD
AD7303
1/2
CMP04
PASS/FAIL
10kΩ
SYNC
SYNC
DIN
DIN
DATA
DIN
V B
OUT
SCLK
SCLK
1/6 74HC05
AGND
GND
Figure 32. AD7303 in Opto-Isolated Interface
Decoding Multiple AD7303
Figure 34. Window Detector Using AD7303
Programmable Current Source
The SYNC pin on the AD7303 can be used in applications to
decode a number of DACs. In this application, all DACs in the
system receive the same serial clock and serial data, but only the
SYNC to one of the DACs will be active at any one time allow-
ing access to two channels in this eight-channel system. The
74HC139 is used as a 2- to 4-line decoder to address any of the
DACs in the system. To prevent timing errors from occurring,
the enable input should be brought to its inactive state while the
coded address inputs are changing state. Figure 33 shows a dia-
gram of a typical setup for decoding multiple AD7303 devices in
a system.
Figure 35 shows the AD7303 used as the control element of a
programmable current source. In this circuit, the full-scale cur-
rent is set to 1 mA. The output voltage from the DAC is applied
across the current setting resistor of 4.7 kΩ in series with the
full-scale setting resistor of 470 Ω. Suitable transistors to place
in the feedback loop of the amplifier include the BC107 and the
2N3904, which enable the current source to operate from a min
VSOURCE of 6 V. The operating range is determined by the oper-
ating characteristics of the transistor. Suitable amplifiers in-
clude the AD820 and the OP295, both having rail-to-rail
operation on their outputs. The current for any digital input
code can be calculated as follows:
AD7303
I = 2 × VREF × D/(5E + 3 × 256) mA
SCLK
SYNC
V
DD
= +5V
DIN
DIN
V
DD
SCLK
0.1µF
0.1µF
10µF
V
CC
V
SOURCE
1G
1A
1B
1Y0
1Y1
1Y2
ENABLE
AD7303
V
+5V
IN
SYNC
DIN
LOAD
CODED
ADDRESS
V
DD
EXT
REF
GND
V
OUT
REF
V A
OUT
AD820/
OP295
SCLK
74HC139
DGND
1Y3
AD7303
SCLK
DIN
4.7kΩ
470Ω
AD7303
AD780/ REF192
WITH V = +5V
DD
SYNC
DIN
SYNC
GND
SCLK
SERIAL
INTERFACE
AD7303
SYNC
DIN
Figure 35. Programmable Current Source
SCLK
Figure 33. Decoding Multiple AD7303 Devices in a System
REV. 0
–13–
AD7303
Inductance (ESI), like the common ceramic types that provide a
low impedance path to ground at high frequencies to handle
transient currents due to internal logic switching.
Power Supply Bypassing and Grounding
In any circuit where accuracy is important, careful consideration
of the power supply and ground return layout helps to ensure
the rated performance. The printed circuit board on which the
AD7303 is mounted should be designed so that the analog and
digital sections are separated, and confined to certain areas of
the board. If the AD7303 is in a system where multiple
devices require an AGND to DGND connection, the connec-
tion should be made at one point only. The star ground point
should be established as closely as possible to the AD7303. The
AD7303 should have ample supply bypassing of 10 µF in paral-
lel with 0.1 µF on the supply located as closely to the package as
possible, ideally right up against the device. The 10 µF capaci-
tors are the tantalum bead type. The 0.1 µF capacitor should
have low Effective Series Resistance (ESR) and Effective Series
The power supply lines of the AD7303 should use as large a
trace as possible to provide low impedance paths and reduce the
effects of glitches on the power supply line. Fast switching sig-
nals such as clocks should be shielded with digital ground to
avoid radiating noise to other parts of the board, and should
never be run near the reference inputs. Avoid crossover of digi-
tal and analog signals. Traces on opposite sides of the board
should run at right angles to each other. This reduces the effects of
feedthrough through the board. A microstrip technique is by far
the best, but not always possible with a double-sided board. In
this technique, the component side of the board is dedicated to
ground plane while signal traces are placed on the solder side.
AD7303 to 68HC11 Interface Program Source Code
*
PORTC
EQU
$1003
Port C Control Register
*
"SYNC, 0, 0, 0, 0, 0, 0, 0"
DDRC
PORTD
*
EQU
EQU
$1007
$1008
Port C Data Direction
Port D Data Register
"0, 0, 0, SCLK, DIN, 0, 0, 0"
Port D Data Direction
DDRD
SPCR
*
EQU
EQU
$1009
$1028
SPI Control Register
"SPIE, SPE, DWOM, MSTR, CPOL, CPHA, SPR1, SPR0"
SPI Status Register
SPSR
*
EQU
EQU
$1029
$102A
"SPIF, WCOL, 0, MODF, 0, 0, 0, 0"
SPI Data Register, Read Buffer, Write Shifter
SPDR
*
* SDI RAM Variables:
DIN 1 is eight MSBs, Control BYTE
DIN 2 is eight LSBs, Data BYTE
DAC requires 2*8-bit Writes
DIN1
DIN2
*
EQU
EQU
$00
$01
DIN BYTE 1: " INT/EXT, X, LDAC, PDB, PBA, A/B, CR1, CR0"
DIN BYTE 2: " DB7, DB6, DB5, DB4, DB3, DB2, DB1, DB0"
ORG
LDS
$C000
Start of users ram
INIT
*
#$CFFF
Top of C page Ram
LDAA
#$80
1, 0, 0, 0, 0, 0, 0, 0
SYNC is High
*
STAA
LDAA
STAA
PORTC
#$80
Initialize Port C Outputs
1, 0, 0, 0, 0, 0, 0, 0
SYNC enabled as output
DDRC
*
*
LDAA
STAA
#$00
0, 0, 0, 0, 0, 0, 0, 0
SCLK is low, DIN is low
Initialize Port D outputs
PORTD
–14–
REV. 0
AD7303
LDAA
#$18
0, 0, 0, 1, 1, 0, 0, 0
*
*
SCLK and DIN enabled as outputs
LDAA
STAA
#$53
SPCR
SPI on, Master mode, CPOL=0, CPHA=0, Clock rate =E/32
BSR
JMP
UPDATE
#$E000
Update AD7303 output.
Restart.
*
UPDATE
PSHX
PSHY
PSHA
Save relevant registers.
*
*
LDAA
STAA
#$00
Control Word "0, 0, 0, 0, 0, 0, 0, 0"
DIN 1
Load both DAC A and DAC B DAC registers from shift register
with internal reference selected.
LDAA
STAA
#$AA
DIN 2
Data Word "1, 0, 1, 0, 1, 0, 1, 0"
LDX
LDY
#DIN1
#$1000
Stack pointer at first first byte to send via DIN 1.
Stack pointer at on chip registers.
*
BCLR
LDAA
STAA
PORTC,Y $80
0,X
Assert SYNC.
TRANSFER
Get BYTE to transfer via SPI.
Write to DIN register to start transfer.
SPDR
*
WAIT
LDAA
BPL
SPSR
Wait for SPIF to be set to indicate that transfer has been completed.
WAIT
SPIF is the MSB of the SPCR. SPIF is automatically reset if in a set
state when the status register is read.
*
INX
CPX
BNE
Increment counter for transfer of second byte.
16 bits transferred?
#DIN 2+1
TRANSFER
If not, transfer second BYTE.
*Execute instruction
BSET
PORTC,Y $80
Bring SYNC back high.
Restore registers.
PULA
PULY
PULX
RTS
Return to main program.
REV. 0
–15–
AD7303
OUTLINE DIMENSIONS
Dimensions shown in inches and (mm).
8-Pin Plastic DIP
(N-8)
0.430 (10.92)
0.348 (8.84)
8
5
4
0.280 (7.11)
0.240 (6.10)
1
0.325 (8.25)
0.300 (7.62)
0.060 (1.52)
0.015 (0.38)
PIN 1
0.195 (4.95)
0.115 (2.93)
0.210 (5.33)
MAX
0.130
(3.30)
MIN
0.160 (4.06)
0.115 (2.93)
0.015 (0.381)
0.008 (0.204)
SEATING
PLANE
0.100
(2.54)
BSC
0.022 (0.558)
0.014 (0.356)
0.070 (1.77)
0.045 (1.15)
8-Lead SOIC
(SO-8)
0.1968 (5.00)
0.1890 (4.80)
8
1
5
4
0.1574 (4.00)
0.1497 (3.80)
0.2440 (6.20)
0.2284 (5.80)
PIN 1
0.0688 (1.75)
0.0532 (1.35)
0.0196 (0.50)
x 45°
0.0098 (0.25)
0.0040 (0.10)
0.0099 (0.25)
8°
0°
0.0500
(1.27)
BSC
0.0192 (0.49)
0.0138 (0.35)
SEATING
PLANE
0.0098 (0.25)
0.0075 (0.19)
0.0500 (1.27)
0.0160 (0.41)
8-Lead microSOIC
(RM-8)
0.122 (3.10)
0.114 (2.90)
5
4
8
1
0.199 (5.05)
0.187 (4.75)
0.122 (3.10)
0.114 (2.90)
PIN 1
0.0256 (0.65) BSC
0.120 (3.05)
0.112 (2.84)
0.120 (3.05)
0.112 (2.84)
0.043 (1.09)
0.037 (0.94)
0.006 (0.15)
0.002 (0.05)
33°
27°
0.018 (0.46)
0.011 (0.28)
0.003 (0.08)
0.028 (0.71)
0.016 (0.41)
SEATING
PLANE
0.008 (0.20)
–16–
REV. 0
相关型号：
AD7303BRM-REEL
SERIAL INPUT LOADING, 1.2 us SETTLING TIME, 8-BIT DAC, PDSO8, MICRO, SOIC-8
ROCHESTER
AD7303BRM-REEL7
SERIAL INPUT LOADING, 1.2 us SETTLING TIME, 8-BIT DAC, PDSO8, MICRO, SOIC-8
ROCHESTER
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