AD7440BRMZ [ADI]
Differential Input, 1 MSPS, 12- (AD7450A) & 10-Bit (AD7440) ADCs;
| 型号： | AD7440BRMZ |
| 厂家： | 
ADI |
| 描述： | Differential Input, 1 MSPS, 12- (AD7450A) & 10-Bit (AD7440) ADCs |
| 文件： | 总28页 (文件大小：770K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
Differential Input, 1 MSPS
10-Bit and 12-Bit ADCs in an 8-Lead SOT-23
AD7440/AD7450A
FUNCTIONAL BLOCK DIAGRAM
DD
FEATURES
V
Fast throughput rate: 1 MSPS
Specified for VDD of 3 V and 5 V
Low power at max throughput rate:
4 mW max at 1 MSPS with 3 V supplies
9.25 mW max at 1 MSPS with 5 V supplies
Fully differential analog input
Wide input bandwidth:
V
V
IN+
12-BIT
SUCCESSIVE
APPROXIMATION
ADC
T/H
IN–
V
REF
70 dB SINAD at 100 kHz input frequency
Flexible power/serial clock speed management
No pipeline delays
SCLK
SDATA
High speed serial interface:
AD7440/AD7450A
CONTROL LOGIC
CS
SPI®/QSPI™/MICROWIRE™/DSP compatible
Power-down mode: 1 µA max
8-lead SOT-23 and MSOP packages
GND
APPLICATIONS
Figure 1.
Transducer interface
Battery-powered systems
Data acquisition systems
Portable instrumentation
Motor control
CS
on the falling edge of ; the conversion is also initiated at this
point. The SAR architecture of these parts ensures that there are
no pipeline delays. The AD7440 and the AD7450A use ad-
vanced design techniques to achieve very low power dissipation
at high throughput rates.
PRODUCT HIGHLIGHTS
GENERAL DESCRIPTION
The AD7440/AD7450A1 are 10-bit and 12-bit high speed, low
power, successive approximation (SAR) analog-to-digital
converters with a fully differential analog input. These parts
operate from a single 3 V or 5 V power supply and use advanced
design techniques to achieve very low power dissipation at
throughput rates up to 1 MSPS. The SAR architecture of these
parts ensures that there are no pipeline delays.
1. Operation with either 3 V or 5 V power supplies.
2. High throughput with low power consumption.
With a 3 V supply, the AD7440/AD7450A offer 4 mW
max power consumption for 1 MSPS throughput.
3. Fully differential analog input.
4. Flexible power/serial clock speed management.
The conversion rate is determined by the serial clock,
allowing the power to be reduced as the conversion time
is reduced through the serial clock speed increase. These
parts also feature a shutdown mode to maximize power
efficiency at lower throughput rates.
The parts contain a low noise, wide bandwidth, differential
track-and-hold amplifier (T/H) that can handle input
frequencies up to 3.5 MHz. The reference voltage is applied
externally to the VREF pin and can be varied from 100 mV to
3.5 V depending on the power supply and what suits the
application. The value of the reference voltage determines the
common-mode voltage range of the part. With this truly
differential input structure and variable reference input, the user
can select a variety of input ranges and bias points.
5. Variable voltage reference input.
6. No pipeline delay.
CS
7. Accurate control of the sampling instant via a
once-off conversion control.
input and
8. ENOB > eight bits typically with 100 mV reference.
The conversion process and data acquisition are controlled
CS
using
and the serial clock, allowing the device to interface
with microprocessors or DSPs. The input signals are sampled
1 Protected by U.S. Patent Number 6,681,332.
Rev. B
Information furnished by Analog Devices is believed to be accurate and reliable.
However, no responsibility is assumed by Analog Devices for its use, nor for any
infringements of patents or other rights of third parties that may result from its use.
Specifications subject to change without notice. No license is granted by implication
or otherwise under any patent or patent rights of Analog Devices. Trademarks and
registered trademarks are the property of their respective owners.
One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A.
Tel: 781.329.4700
Fax: 781.326.8703
www.analog.com
© 2004 Analog Devices, Inc. All rights reserved.
AD7440/AD7450A
TABLE OF CONTENTS
AD7440–Specifications.................................................................... 3
Digital Inputs .............................................................................. 20
Reference ..................................................................................... 20
Single-Ended Operation............................................................ 20
Serial Interface............................................................................ 21
Modes of Operation ....................................................................... 23
Normal Mode.............................................................................. 23
Power-Down Mode.................................................................... 23
Power-Up Time .......................................................................... 24
Power vs. Throughput Rate....................................................... 24
Microprocessor and DSP Interfacing ...................................... 25
Grounding and Layout Hints.................................................... 26
Evaluating the AD7440/AD7450A Performance................... 26
Outline Dimensions....................................................................... 27
Ordering Guide............................................................................... 28
AD7450A–Specifications................................................................. 5
Timing Specifications....................................................................... 7
Absolute Maximum Ratings............................................................ 8
ESD Caution.................................................................................. 8
Pin Configurations and Function Descriptions ........................... 9
Terminology .................................................................................... 10
AD7440/AD7450A–Typical Performance Characteristics ....... 12
Circuit Information........................................................................ 15
Converter Operation.................................................................. 15
ADC Transfer Function............................................................. 15
Typical Connection Diagram ................................................... 16
Analog Input ............................................................................... 16
Driving Differential Inputs........................................................ 18
REVISION HISTORY
2/04—Data Sheet changed from Rev. A to Rev. B
Added Patent Note .............................................................................. 1
1/04—Data Sheet changed from Rev. 0 to Rev. A
Updated Format.................................................................... Universal
Changes to General Description ....................................................... 1
Changes to Table 1 footnotes ............................................................. 3
Changes to Table 2 footnotes ............................................................. 5
Changes to Table 3 footnotes ............................................................. 7
Rev. B | Page 2 of 28
AD7440/AD7450A
AD7440–SPECIFICATIONS
Table 1. VDD = 2.7 V to 3.6 V, fSCLK = 18 MHz, fS = 1 MSPS, VREF = 2.0 V; VDD = 4.75 V to 5.25 V, fSCLK = 18 MHz, fS = 1 MSPS,
VREF = 2.5 V; VCM1 = VREF; TA= TMIN to TMAX, unless otherwise noted. Temperature range for B Version –40°C to +85°C.
Parameter
Test Conditions/Comments
B Version
Unit
DYNAMIC PERFORMANCE
Signal-to-(Noise + Distortion) (SINAD)2
Total Harmonic Distortion (THD)2
Peak Harmonic or Spurious Noise2
Intermodulation Distortion (IMD)2
Second-Order Terms
fIN = 100 kHz
61
–74
–76
dB min
dB max
dB max
–82 dB typ
–82 dB typ
fa = 90 kHz, fb = 110 kHz
–83
–83
5
50
20
dB typ
dB typ
ns typ
ps typ
MHz typ
MHz typ
Third-Order Terms
Aperture Delay2
Aperture Jitter2
Full Power Bandwidth2, 3
@ –3 dB
@ –0.1 dB
2.5
DC ACCURACY
Resolution
10
0.5
0.5
2.5
1
Bits
Integral Nonlinearity (INL)2
Differential Nonlinearity (DNL)2
Zero-Code Error2
Positive Gain Error2
Negative Gain Error2
ANALOG INPUT
LSB max
LSB max
LSB max
LSB max
LSB max
Guaranteed no missed codes to 10 bits
1
4
Full-Scale Input Span
Absolute Input Voltage
VIN+
2 × VREF
VIN+ – VIN–
V
VCM = VREF
VCM = VREF
VCM VREF/2
VCM VREF/2
1
V
V
VIN–
DC Leakage Current
Input Capacitance
REFERENCE INPUT
VREF Input Voltage
µA max
pF typ
When in track-and-hold
30/10
VDD = 4.75 V to 5.25 V ( 1ꢀ tolerance for
specified performance)
2.55
V
VDD = 2.7 V to 3.6 V ( 1ꢀ tolerance for specified
performance)
2.06
1
10/30
V
DC Leakage Current
VREF Input Capacitance
LOGIC INPUTS
µA max
pF typ
When in track-and-hold
Input High Voltage, VINH
Input Low Voltage, VINL
Input Current, IIN
2.4
0.8
1
V min
V max
µA max
pF max
Typically 10 nA, VIN = 0 V or VDD
7
Input Capacitance, CIN
10
LOGIC OUTPUTS
Output High Voltage, VOH
VDD = 4.75 V to 5.25 V; ISOURCE = 200 µA
2.8
V min
VDD = 2.7 V to 3.6 V; ISOURCE = 200 µA
ISINK = 200 µA
2.4
0.4
1
10
V min
Output Low Voltage, VOL
Floating-State Leakage Current
Floating-State Output Capacitance7
Output Coding
V max
µA max
pF max
Twos Complement
Rev. B | Page 3 of 28
AD7440/AD7450A
Parameter
Test Conditions/Comments
B Version
Unit
CONVERSION RATE
Conversion Time
888 ns with an 18 MHz SCLK
Sine wave input
Step input
16
SCLK cycles
ns max
ns max
Track-and-Hold Acquisition Time2
200
290
1
Throughput Rate
POWER REQUIREMENTS
VDD
MSPS max
Range: 3 V + 20ꢀ/–10ꢀ; 5 V 5ꢀ
2.7/5.25
V min/V max
8
IDD
Normal Mode (Static)
Normal Mode (Operational)
SCLK on or off
0.5
1.95
1.45
1
mA typ
mA max
mA max
µA max
VDD = 4.75 V to 5.25 V
VDD = 2.7 V to 3.6 V
SCLK on or off
Full Power-Down Mode
Power Dissipation
Normal Mode (Operational)
VDD = 5 V, 1.55 mW typ for 100 kSPS9
VDD = 3 V, 0.6 mW typ for 100 kSPS9
VDD = 5 V, SCLK on or off
9.25
4
5
mW max
mW max
µW max
µW max
Full Power-Down
VDD = 3 V, SCLK on or off
3
1 Common-mode voltage. The input signal can be centered on a dc common-mode voltage in the range specified in Figure 28 and Figure 29.
2 See Terminology section.
3 Analog inputs with slew rates exceeding 27 V/µs (full-scale input sine wave > 3.5 MHz) within the acquisition time may cause the converter to return an
incorrect result.
4 Because the input spans of VIN+ and VIN– are both VREF and are 180°out of phase, the differential voltage is 2 × VREF
.
5 The AD7440 is functional with a reference input from 100 mV and for VDD = 5 V; the reference can range up to 3.5 V.
6 The AD7440 is functional with a reference input from 100 mV and for VDD = 3 V; the reference can range up to 2.2 V.
7 Guaranteed by characterization.
8 Measured with a midscale dc input.
9 See Power vs. Throughput section.
Rev. B | Page 4 of 28
AD7440/AD7450A
AD7450A–SPECIFICATIONS
Table 2. VDD = 2.7 V to 3.6 V, fSCLK = 18 MHz, fS = 1 MSPS, VREF = 2.0 V; VDD = 4.75 V to 5.25 V, fSCLK = 18 MHz, fS = 1 MSPS,
VREF = 2.5 V; VCM1 = VREF; TA = TMIN to TMAX, unless otherwise noted. Temperature range for B Version –40°C to +85°C.
Parameter
Test Conditions/Comments
B Version
Unit
DYNAMIC PERFORMANCE
Signal-to-(Noise + Distortion) (SINAD)2
Total Harmonic Distortion (THD)2
fIN = 100 kHz
70
dB min
dB max
dB max
dB max
dB max
VDD = 4.75 V to 5.25 V, –86 dB typ
VDD = 2.7 V to 3.6 V, –84 dB typ
VDD = 4.75 V to 5.25 V, –86 dB typ
VDD = 2.7 V to 3.6 V, –84 dB typ
fa = 90 kHz, fb = 110 kHz
–76
–74
–76
–74
Peak Harmonic or Spurious Noise2
Intermodulation Distortion (IMD)2
Second-Order Terms
Third-Order Terms
Aperture Delay2
Aperture Jitter2
Full Power Bandwidth2, 3
–89
–89
5
50
20
dB typ
dB typ
ns typ
ps typ
MHz typ
MHz typ
@ –3 dB
@ –0.1 dB
2.5
DC ACCURACY
Resolution
12
1
0.95
6
2
2
Bits
Integral Nonlinearity (INL)2
Differential Nonlinearity (DNL)2
Zero-Code Error2
Positive Gain Error2
Negative Gain Error2
ANALOG INPUT
LSB max
LSB max
LSB max
LSB max
LSB max
Guaranteed no missed codes to 12 bits
4
Full-Scale Input Span
Absolute Input Voltage
VIN+
2 × VREF
VIN+ – VIN–
V
VCM = VREF
VCM = VREF
VCM VREF/2
VCM VREF/2
1
V
V
VIN–
DC Leakage Current
Input Capacitance
REFERENCE INPUT
VREF Input Voltage
µA max
pF typ
When in track-and-hold
30/10
VDD = 4.75 V to 5.25 V
( 1ꢀ tolerance for specified performance)
VDD = 2.7 V to 3.6 V
2.55
2.06
V
V
( 1ꢀ tolerance for specified performance)
DC Leakage Current
VREF Input Capacitance
LOGIC INPUTS
1
µA max
pF typ
When in track-and-hold
10/30
Input High Voltage, VINH
Input Low Voltage, VINL
Input Current, IIN
2.4
0.8
1
V min
V max
µA max
pF max
Typically 10 nA, VIN = 0 V or VDD
7
Input Capacitance, CIN
10
LOGIC OUTPUTS
Output High Voltage, VOH
VDD = 4.75 V to 5.25 V; ISOURCE = 200 µA
VDD = 2.7 V to 3.6 V; ISOURCE = 200 µA
ISINK = 200 µA
2.8
2.4
0.4
1
V min
V min
V max
µA max
pF max
Output Low Voltage, VOL
Floating-State Leakage Current
Floating-State Output Capacitance7
Output Coding
10
Twos Complement
Rev. B | Page 5 of 28
AD7440/AD7450A
Parameter
Test Conditions/Comments
B Version
Unit
CONVERSION RATE
Conversion Time
888 ns with an 18 MHz SCLK
Sine wave input
Step input
16
SCLK cycles
ns max
ns max
Track-and-Hold Acquisition Time2
200
290
1
Throughput Rate
POWER REQUIREMENTS
VDD
MSPS max
Range: 3 V + 20ꢀ/–10ꢀ; 5 V 5ꢀ
2.7/5.25
V min/V max
8
IDD
Normal Mode (Static)
Normal Mode (Operational)
SCLK on or off
0.5
1.95
1.45
1
mA typ
mA max
mA max
µA max
VDD = 4.75 V to 5.25 V
VDD = 2.7 V to 3.6 V
SCLK on or off
Full Power-Down Mode
Power Dissipation
Normal Mode (Operational)
VDD = 5 V, 1.55 mW typ for 100 kSPS9
VDD = 3 V, 0.6 mW typ for 100 kSPS9
VDD = 5 V, SCLK on or off
9.25
4
5
mW max
mW max
µW max
µW max
Full Power-Down
VDD = 3 V, SCLK on or off
3
1 Common-mode voltage. The input signal can be centered on a dc common-mode voltage in the range specified in Figure 28 and Figure 29.
2 See Terminology section.
3 Analog inputs with slew rates exceeding 27 V/µs (full-scale input sine wave > 3.5 MHz) within the acquisition time may cause the converter to return an
incorrect result.
4 Because the input spans of VIN+ and VIN– are both VREF and are 180° out of phase, the differential voltage is 2 × VREF
.
5 The AD7450A is functional with a reference input from 100 mV and for VDD = 5 V; the reference can range up to 3.5 V.
6 The AD7450A is functional with a reference input from 100 mV and for VDD = 3 V; the reference can range up to 2.2 V.
7 Guaranteed by characterization.
8 Measured with a midscale dc input.
9 See Power vs. Throughput section.
Rev. B | Page 6 of 28
AD7440/AD7450A
TIMING SPECIFICATIONS
Guaranteed by characterization. All input signals are specified with tr = tf = 5 ns (10% to 90% of VDD) and timed from a voltage level of
1.6 V. See Figure 2, Figure 3, and the Serial Interface section.
Table 3. VDD = 2.7 V to 3.6 V, fSCLK = 18 MHz, fS = 1 MSPS, VREF = 2.0 V; VDD = 4.75 V to 5.25 V, fSCLK = 18 MHz, fS = 1 MSPS,
VREF = 2.5 V; VCM1 = VREF; TA = TMIN to TMAX, unless otherwise noted.
Parameter
Limit at TMIN, TMAX
Unit
Description
2
fSCLK
10
18
kHz min
MHz max
tCONVERT
16 × tSCLK
888
60
tSCLK = 1/fSCLK
ns max
ns min
ns min
ns min
ns max
ns max
ns min
ns min
ns min
ns min
ns max
µs max
CS
tQUIET
t1
Minimum quiet time between the end of a serial read and the next falling edge of
CS
10
Minimum
CS
pulse width
t2
10
falling edge to SCLK falling edge setup time
3
CS
t3
20
Delay from falling edge until SDATA three-state disabled
3
t4
40
Data access time after SCLK falling edge
SCLK high pulse width
SCLK low pulse width
SCLK edge to data valid hold time
SCLK falling edge to SDATA three-state enabled
SCLK falling edge to SDATA three-state enabled
Power-up time from full power-down
t5
t6
t7
0.4 tSCLK
0.4 tSCLK
10
10
35
4
t8
5
tPOWER-UP
1
1 Common-mode voltage.
2 Mark/space ratio for the SCLK input is 40/60 to 60/40.
3 Measured with the load circuit of Figure 4 and defined as the time required for the output to cross 0.8 V or 2.4 V with VDD = 5 V or 0.4 V or 2.0 V for VDD = 3 V.
4 t8 is derived from the measured time taken by the data outputs to change 0.5 V when loaded with the circuit of Figure 4. The measured number is then extrapolated
back to remove the effects of charging or discharging the 25 pF capacitor. This means that the time, t8, quoted in the Timing Specifications is the true bus relinquish
time of the part and is independent of the bus loading.
5 See Power-Up Time section.
t1
CS
tCONVERT
t2
t3
B
t5
1
2
3
4
5
13
14
t6
15
16
SCLK
t8
t7
t4
tQUIET
THREE-STATE
0
0
0
0
DB11
DB10
DB2
DB1
DB0
SDATA
4 LEADING ZEROS
Figure 2. AD7450A Serial Interface Timing Diagram
t1
CS
tCONVERT
t2
t3
B
t5
1
2
3
4
5
13
14
t6
15
16
SCLK
t8
t7
DB8
t4
tQUIET
0
0
0
0
DB9
DB0
0
0
SDATA
THREE-STATE
4 LEADING ZEROS
2 TRAILING ZEROS
Figure 3. AD7440 Serial Interface Timing Diagram
Rev. B | Page 7 of 28
AD7440/AD7450A
ABSOLUTE MAXIMUM RATINGS
TA = 25°C, unless otherwise noted.
Table 4.
1.6mA
I
OL
Parameter
Rating
TO OUTPUT
PIN
1.6V
VDD to GND
VIN+ to GND
VIN– to GND
Digital Input Voltage to GND
Digital Output Voltage to GND
VREF to GND
Input Current to Any Pin Except Supplies1
Operating Temperature Range
Commercial (B Version)
Storage Temperature Range
Junction Temperature
θJA Thermal Impedance
MSOP
–0.3 V to +7 V
C
25pF
L
–0.3 V to VDD + 0.3 V
–0.3 V to VDD + 0.3 V
–0.3 V to +7 V
–0.3 V to VDD + 0.3 V
–0.3 V to VDD + 0.3 V
10 mA
200µA
I
OH
Figure 4. Load Circuit for Digital Output Timing Specifications
–40°C to +85°C
–65°C to +150°C
150°C
205.9°C/W
211.5°C/W
SOT-23
θJC Thermal Impedance
MSOP
SOT-23
43.74°C/W
91.99°C/W
Lead Temperature, Soldering
Vapor Phase (60 secs)
Infrared (15 secs)
ESD
215°C
220°C
1 kV
Stresses above those listed under Absolute Maximum Ratings
may cause permanent damage to the device. This is a stress
rating only; functional operation of the device at these or any
other conditions above those listed in the operational sections
of this specification is not implied. Exposure to absolute
maximum rating conditions for extended periods may affect
device reliability.
1 Transient currents of up to 100 mA do not cause SCR latch up.
ESD CAUTION
ESD (electrostatic discharge) sensitive device. Electrostatic charges as high as 4000 V readily accumulate on the
human body and test equipment and can discharge without detection. Although this product features
proprietary ESD protection circuitry, permanent damage may occur on devices subjected to high energy
electrostatic discharges. Therefore, proper ESD precautions are recommended to avoid performance
degradation or loss of functionality.
Rev. B | Page 8 of 28
AD7440/AD7450A
PIN CONFIGURATIONS AND FUNCTION DESCRIPTIONS
V
1
2
3
4
8
7
6
5
V
V
1
2
3
4
8
7
6
5
V
V
V
REF
DD
DD
REF
IN+
IN–
AD7440/
AD7440/
V
SCLK
SDATA
CS
SCLK
SDATA
CS
IN+
AD7450A
AD7450A
V
IN–
TOP VIEW
(Not to Scale)
TOP VIEW
(Not to Scale)
GND
GND
Figure 6. Pin Configuration for 8-Lead MSOP
Figure 5. Pin Configuration for 8-Lead SOT-23
Table 5. Pin Function Descriptions
Mnemonic Function
VREF
Reference Input for the AD7440/AD7450A. An external reference must be applied to this input. For a 5 V power supply, the
reference is 2.5 V ( 1ꢀ) for specified performance. For a 3 V power supply, the reference is 2 V ( 1ꢀ) for specified
performance. This pin should be decoupled to GND with a capacitor of at least 0.1 µF. See the Reference section for more
details.
VIN+
VIN–
Positive Terminal for Differential Analog Input.
Negative Terminal for Differential Analog Input.
GND
Analog Ground. Ground reference point for all circuitry on the AD7440/AD7450A. All analog input signals and any external
reference signal should be referred to this GND voltage.
CS
Chip Select. Active low logic input. This input provides the dual function of initiating a conversion on the AD7440/AD7450A
and framing the serial data transfer.
SDATA
Serial Data. Logic output. The conversion result from the AD7440/AD7450A is provided on this output as a serial data stream.
The bits are clocked out on the falling edge of the SCLK input. The data stream of the AD7450A consists of four leading zeros
followed by the 12 bits of conversion data, which are provided MSB first; the data stream of the AD7440 consists of four
leading zeros, followed by the 10 bits of conversion data, followed by two trailing zeros. In both cases, the output coding is
twos complement.
SCLK
VDD
Serial Clock. Logic input. SCLK provides the serial clock for accessing data from the part. This clock input is also used as the
clock source for the conversion process.
Power Supply Input. VDD is 3 V (+20ꢀ/–10ꢀ) or 5 V ( 5ꢀ). This supply should be decoupled to GND with a 0.1 µF capacitor
and a 10 µF tantalum capacitor in parallel.
Rev. B | Page 9 of 28
AD7440/AD7450A
TERMINOLOGY
Signal-to-(Noise + Distortion) Ratio
The AD7440/AD7450A is tested using the CCIF standard of
two input frequencies near the top end of the input bandwidth.
In this case, the second-order terms are distanced in frequency
from the original sine waves, while the third-order terms are at
a frequency close to the input frequencies. As a result, the
second- and third-order terms are specified separately. The
calculation of the intermodulation distortion is as per the THD
specification, where it is the ratio of the rms sum of the
individual distortion products to the rms amplitude of the sum
of the fundamentals, expressed in dB.
This is the measured ratio of signal to (noise + distortion) at the
output of the ADC. The signal is the rms amplitude of the
fundamental. Noise is the sum of all nonfundamental signals
up to half the sampling frequency (fS/2), excluding dc. The
ratio is dependent on the number of quantization levels in the
digitization process; the more levels, the smaller the quanti-
zation noise. The theoretical signal-to-(noise + distortion) ratio
for an ideal N-bit converter with a sine wave input is given by
the following:
Aperture Delay
Signal-to-(Noise + Distortion) = (6.02N + 1.76)dB.
This is the amount of time from the leading edge of the
sampling clock until the ADC actually takes the sample.
Thus for a 12-bit converter, this is 74 dB; and for a 10-bit
converter, this is 62 dB.
Aperture Jitter
Total Harmonic Distortion (THD)
This is the sample-to-sample variation in the effective point in
time at which the actual sample is taken.
THD is the ratio of the rms sum of harmonics to the
fundamental. For the AD7440/AD7450A, it is defined as
Full Power Bandwidth
2
2
2
2
V
2
2 +V
3
+V
4
+V
5
+V
6
THD(dB) = 20 log
The full power bandwidth of an ADC is the input frequency at
which the amplitude of the reconstructed fundamental is
reduced by 0.1 dB or 3 dB for a full-scale input.
V
1
where V1 is the rms amplitude of the fundamental and V2, V3,
V4, V5, and V6 are the rms amplitudes of the second to the sixth
harmonics.
Common-Mode Rejection Ratio (CMRR)
The common-mode rejection ratio is the ratio of the power
in the ADC output at full-scale frequency, f, to the power of a
100 mV p-p sine wave applied to the common-mode voltage of
VIN+ and VIN– of frequency fS as follows:
Peak Harmonic or Spurious Noise
Peak harmonic (spurious noise) is the ratio of the rms value of
the next largest component in the ADC output spectrum (up to
fS/2 and excluding dc) to the rms value of the fundamental.
Normally, the value of this specification is determined by the
largest harmonic in the spectrum, but for ADCs where the
harmonics are buried in the noise floor, it is a noise peak.
CMRR (dB) = 10 log (Pf/Pfs)
Pf is the power at the frequency f in the ADC output; Pfs is the
power at frequency fS in the ADC output.
Intermodulation Distortion
Integral Nonlinearity (INL)
With inputs consisting of sine waves at two frequencies,
fa and fb, any active device with nonlinearities creates distortion
products at the sum and difference frequencies of mfa nfb
where m, n = 0, 1, 2, 3, and so on. Intermodulation distortion
terms are those for which neither m nor n is equal to 0. For
example, the second-order terms include (fa + fb) and (fa – fb),
while the third-order terms include (2fa + fb), (2fa – fb),
(fa + 2fb), and (fa – 2fb).
This is the maximum deviation from a straight line passing
through the endpoints of the ADC transfer function.
Differential Nonlinearity (DNL)
This is the difference between the measured and the ideal
1 LSB change between any two adjacent codes in the ADC.
Zero-Code Error
This is the deviation of the midscale code transition
(111...111 to 000...000) from the ideal VIN+ − VIN– (i.e., 0 LSB).
Rev. B | Page 10 of 28
AD7440/AD7450A
Positive Gain Error
Power Supply Rejection Ratio (PSRR)
This is the deviation of the last code transition (011...110 to
011...111) from the ideal VIN+ – VIN– (i.e., +VREF − 1 LSB), after
the zero code error has been adjusted out.
The power supply rejection ratio is the ratio of the power in
the ADC output at full-scale frequency, f, to the power of a
100 mV p-p sine wave applied to the ADC VDD supply of
frequency fS. The frequency of this input varies from 1 kHz to
1 MHz.
Negative Gain Error
This is the deviation of the first code transition (100...000 to
100...001) from the ideal VIN+ − VIN– (i.e., –VREF + 1 LSB),
after the zero code error has been adjusted out.
PSRR (dB) = 10log(Pf/PfS)
Pf is the power at frequency f in the ADC output; Pfs is the
power at frequency fS in the ADC output.
Track-and-Hold Acquisition Time
The track-and-hold acquisition time is the minimum time
required for the track-and-hold amplifier to remain in track
mode for its output to reach and settle to within 0.5 LSB of the
applied input signal.
Rev. B | Page 11 of 28
AD7440/AD7450A
AD7440/AD7450A–TYPICAL PERFORMANCE CHARACTERISTICS
TA = 25°C, fS = 1 MSPS, fSCLK = 18 MHz, unless otherwise noted.
75
70
65
60
55
0
8192 POINT FFT
fSAMPLE = 1MSPS
fIN = 100kSPS
V
= 5.25V
V
= 4.75V
DD
DD
–20
SINAD = +71.7dB
THD = –82dB
–40
SFDR = –83dB
V
V
= 3.6V
DD
DD
–60
= 2.7V
–80
–100
–120
–140
10
100
FREQUENCY (kHz)
1000
0
100
200
300
400
500
FREQUENCY (kHz)
Figure 7. AD7450A SINAD vs. Analog Input Frequency for Various
Supply Voltages
Figure 10. AD7450A Dynamic Performance with VDD = 5 V
0
–10
–20
–30
–40
–50
–60
1.0
0.8
0.6
0.4
0.2
0
–0.2
–0.4
–0.6
–0.8
–1.0
V
= 3V
DD
–70
–80
–90
V
= 5V
DD
–100
10
100
1000
10000
0
1024
2048
3072
4096
FREQUENCY (kHz)
CODE
Figure 8. CMRR vs. Frequency for VDD = 5 V and 3 V
Figure 11. Typical DNL for the AD7450A for VDD = 5 V
0
–20
1.0
0.8
100mV p-p SINEWAVE ON V
DD
NO DECOUPLING ON V
DD
0.6
–40
0.4
0.2
–60
V
DD
= 3V
0
–0.2
–0.4
–0.6
–0.8
–1.0
V
= 5V
DD
–80
–100
–120
0
100 200 300 400 500 600 700 800 900 1000
SUPPLY RIPPLE FREQUENCY (kHz)
0
1024
2048
3072
4096
CODE
Figure 9. PSRR vs. Supply Ripple Frequency without Supply Decoupling
Figure 12. Typical INL for the AD7450A for VDD = 5 V
Rev. B | Page 12 of 28
AD7440/AD7450A
3.0
2.5
2.0
1.5
1.0
0.5
0
2.5
2.0
1.5
1.0
POSITIVE INL
0.5
0
POSITIVE DNL
NEGATIVE DNL
–0.5
–1.0
–1.5
–2.0
NEGATIVE INL
–0.5
–1.0
0
0.5
1.0
1.5
V
2.0
(V)
2.5
3.0
3.5
0
0.5
1.0
1.5
2.0 2.2
2.5
V
(V)
REF
REF
Figure 13. Change in DNL vs. VREF for the AD7450A for VDD = 5 V
Figure 16. Change in INL vs. VREF for the AD7450A for VDD = 3 V
2.5
2.0
1.5
1.0
8
7
6
V
= 5V
DD
5
4
3
2
1
0
POSITIVE DNL
0.5
0
V
= 3V
DD
–0.5
–1.0
NEGATIVE DNL
1.5
0
0.5
1.0
2.0 2.2
2.5
0
0.5
1.0
1.5
V
2.0
(V)
2.5
3.0
3.5
V
(V)
REF
REF
Figure 14. Change in DNL vs. VREF for the AD7450A for VDD = 3 V
Figure 17. Change in Zero-Code Error vs. Reference Voltage for
VDD = 5 V and 3 V for the AD7450A
5
4
3
2
12.0
11.5
V
= 3V
DD
11.0
10.5
10.0
9.5
V
= 5V
DD
1
0
POSITIVE INL
NEGATIVE INL
–1
–2
–3
–4
–5
9.0
8.5
8.0
7.5
7.0
0
0.5
1.0
1.5
V
2.0
(V)
2.5
3.0
3.5
0
0.5
1.0
1.5
V
2.0
(V)
2.5
3.0
3.5
REF
REF
Figure 15. Change in INL vs. VREF for the AD7450A for VDD = 5 V
Figure 18. Change in ENOB vs. Reference Voltage for VDD = 5 V and 3 V
for the AD7450A
Rev. B | Page 13 of 28
AD7440/AD7450A
10,000
0.5
0.4
10,000
CODES
V
= V
IN–
IN+
10,000 CONVERSIONS
fS = 1MSPS
9,000
8,000
7,000
6,000
5,000
4,000
3,000
2,000
1,000
0
0.3
0.2
0.1
0
–0.1
–0.2
–0.3
–0.4
–0.5
2044
2045
2046
2047
2048
2049
0
256
512
768
1024
CODE
CODE
Figure 19. Histogram of 10,000 Conversions of a DC Input for the
AD7450A with VDD = 5 V
Figure 21. Typical DNL for the AD7440 for VDD = 5 V
0
0.5
0.4
8192 POINT FFT
fSAMPLE = 1MSPS
fIN = 100kHz
–20
–40
SINAD = +61.6dB
THD = –81.7dB
SFDR = –83.1dB
0.3
0.2
0.1
–60
0
–80
–0.1
–0.2
–0.3
–0.4
–0.5
–100
–120
–140
0
100
200
300
400
500
0
256
512
768
1024
FREQUENCY (kHz)
CODE
Figure 20. AD7440 Dynamic Performance with VDD = 5 V
Figure 22. Typical INL for the AD7440 for VDD = 5 V
Rev. B | Page 14 of 28
AD7440/AD7450A
CIRCUIT INFORMATION
The AD7440/AD7450A are 10-bit and 12-bit fast, low power,
single-supply, successive approximation analog-to-digital
converters (ADCs). They can operate with a 5 V or 3 V power
supply and are capable of throughput rates up to 1 MSPS when
supplied with an 18 MHz SCLK. They require an external
reference to be applied to the VREF pin, with the value of the
reference chosen depending on the power supply and what suits
the application.
When the ADC starts a conversion (Figure 24), SW3 opens and
SW1 and SW2 move to Position B, causing the comparator to
become unbalanced. Both inputs are disconnected once the
conversion begins. The control logic and the charge redistri-
bution DACs are used to add and subtract fixed amounts of
charge from the sampling capacitor arrays to bring the compar-
ator back into a balanced condition. When the comparator is
rebalanced, the conversion is complete. The control logic
generates the ADC’s output code. The output impedances of the
sources driving the VIN+ and the VIN– pins must be matched;
otherwise, the two inputs have different settling times, resulting
in errors.
When they are operated with a 5 V supply, the maximum
reference that can be applied is 3.5 V. When they are operated
with a 3 V supply, the maximum reference that can be applied is
2.2 V (see the Reference section).
CAPACITIVE
DAC
The AD7440/AD7450A have an on-chip differential track-and-
hold amplifier, a successive approximation (SAR) ADC, and a
serial interface, housed in either an 8-lead SOT-23 or an MSOP
package. The serial clock input accesses data from the part and
provides the clock source for the successive approximation
ADC. The AD7440/AD7450A feature a power-down option for
reduced power consumption between conversions. The power-
down feature is implemented across the standard serial interface
as described in the Modes of Operation section.
C
B
A
S
V
V
IN+
SW1
CONTROL
LOGIC
SW3
SW2
A
B
IN–
C
S
V
REF
COMPARATOR
CAPACITIVE
DAC
Figure 24. ADC Conversion Phase
ADC TRANSFER FUNCTION
CONVERTER OPERATION
The output coding for the AD7440/AD7450A is twos
complement. The designed code transitions occur at successive
LSB values (1 LSB, 2 LSBs, and so on). The LSB size of the
AD7450A is 2 × VREF/4096, and the LSB size of the AD7440 is
2 × VREF/1024. The ideal transfer characteristic of the
AD7440/AD7450A is shown in Figure 25.
The AD7440/AD7450A are successive approximation ADCs
based around two capacitive DACs. Figure 23 and Figure 24
show simplified schematics of the ADC in acquisition and
conversion phase, respectively. The ADC is comprised of
control logic, an SAR, and two capacitive DACs. In Figure 23
(acquisition phase), SW3 is closed, SW1 and SW2 are in
Position A, the comparator is held in a balanced condition,
and the sampling capacitor arrays acquire the differential
signal on the input.
1LSB = 2
×
×
V
V
/4096 AD7450A
/1024 AD7440
REF
REF
1LSB = 2
011...111
011...110
CAPACITIVE
DAC
000...001
000...000
111...111
C
B
A
S
V
V
IN+
SW1
CONTROL
LOGIC
SW3
SW2
A
B
IN–
100...010
100...001
100...000
C
S
V
REF
COMPARATOR
1 LSB
0 LSB
+V – 1 LSB
REF
CAPACITIVE
DAC
–V
REF
ANALOG INPUT
(V – V
)
IN+
IN–
Figure 23. ADC Acquisition Phase
Figure 25. AD7440/AD7450A Ideal Transfer Characteristic
Rev. B | Page 15 of 28
AD7440/AD7450A
The common mode is the average of the two signals, that is,
(VIN+ + VIN–)/2 and is therefore the voltage that the two inputs
are centered on. This results in the span of each input being
CM VREF/2. This voltage has to be set up externally, and its
range varies with VREF. As the value of VREF increases, the
common-mode range decreases. When driving the inputs with
an amplifier, the actual common-mode range is determined by
the amplifier’s output voltage swing.
TYPICAL CONNECTION DIAGRAM
Figure 26 shows a typical connection diagram for the
AD7440/AD7450A for both 5 V and 3 V supplies. In this setup,
the GND pin is connected to the analog ground plane of the
system. The VREF pin is connected to either a 2.5 V or a 2 V
decoupled reference source, depending on the power supply, to
set up the analog input range. The common-mode voltage has
to be set up externally and is the value on which the two inputs
are centered. The conversion result is output in a 16-bit word
with 4 leading zeros followed by the MSB of the 12-bit or 10-bit
result. The 10-bit result of the AD7440 is followed by 2 trailing
zeros. For more details on driving the differential inputs and
setting up the common mode, refer to the Driving Differential
Inputs section.
Figure 28 and Figure 29 show how the common-mode range
typically varies with VREF for both a 5 V and a 3 V power supply.
The common mode must be in this range to guarantee the
functionality of the AD7440/AD7450A.
For ease of use, the common mode can be set up to equal VREF
,
resulting in the differential signal being VREF centered on VREF
.
3V/5V
SUPPLY
0.1
µF
10µF
When a conversion takes place, the common mode is rejected,
resulting in a virtually noise-free signal of amplitude –VREF to
+VREF, corresponding to the digital codes of 0 to 4096 in the
case of the AD7450A and 0 to 1024 in the AD7440.
SERIAL
INTERFACE
V
V
DD
V
V
REF
p-p
CM*
CM*
SCLK
IN+
AD7440/
AD7450A
SDATA
CS
µC/µP
4.5
REF
p-p
V
IN–
4.0
GND
V
REF
3.5
3.0
2.5
2.0
1.5
1.0
0.5
0
3.25V
2V/2.5V
REF
V
0.1µF
COMMON-MODE RANGE
*CM IS THE COMMON-MODE VOLTAGE.
Figure 26. Typical Connection Diagram
1.75V
ANALOG INPUT
The analog input of the AD7440/AD7450A is fully differential.
Differential signals have a number of benefits over single-
ended signals, including noise immunity based on the device’s
common-mode rejection, improvements in distortion perfor-
mance, doubling of the device’s available dynamic range, and
flexibility in input ranges and bias points. Figure 27 defines the
fully differential analog input of the AD7440/AD7450A.
0
0.5
1.0
1.5
V
2.0
(V)
2.5
3.0
3.5
REF
Figure 28. Input Common-Mode Range vs. VREF
(VDD = 5 V and VREF (Max) = 3.5 V)
2.5
2.0
1.5
1.0
0.5
0
2V
V
REF
p-p
V
V
IN+
AD7440/
AD7450A
V
REF
p-p
IN–
COMMON-MODE RANGE
COMMON-MODE
VOLTAGE
1V
Figure 27. Differential Input Definitions
The amplitude of the differential signal is the difference
between the signals applied to the VIN+ and VIN– pins
(i.e., VIN+ – VIN–). VIN+ and VIN– are simultaneously driven by two
signals each of amplitude VREF that are 180° out of phase. The
amplitude of the differential signal is therefore –VREF to +VREF
peak-to-peak (2 × VREF). This is true regardless of the common
mode (CM).
0
0.25
0.50
0.75
1.00
(V)
1.25
1.50
1.75
2.00
V
REF
Figure 29. Input Common-Mode Range vs. VREF
(VDD = 3 V and VREF (Max) =2V)
Rev. B | Page 16 of 28
AD7440/AD7450A
Figure 30 shows examples of the inputs to VIN+ and VIN– for
different values of VREF for VDD = 5 V. It also gives the maximum
and minimum common-mode voltages for each reference value
according to Figure 28.
For ac applications, removing high frequency components from
the analog input signal through the use of an RC low-pass filter
on the relevant analog input pins is recommended. In applica-
tions where harmonic distortion and signal-to-noise ratio are
critical, the analog input should be driven from a low impe-
dance source. Large source impedances significantly affect the
ac performance of the ADC. This may necessitate the use of an
input buffer amplifier. The choice of op amp is a function of the
particular application.
REFERENCE = 2V
V
V
IN–
IN+
COMMON-MODE (CM)
2V p-p
CM
= 1V
= 4V
MIN
CM
MAX
When no amplifier is used to drive the analog input, the source
impedance should be limited to low values. The maximum
source impedance depends on the amount of total harmonic
distortion (THD) that can be tolerated. The THD increases as
the source impedance increases, and performance degrades.
Figure 32 shows a graph of THD versus the analog input signal
frequency for different source impedances for VDD = 5 V.
REFERENCE = 2.5V
V
IN–
COMMON-MODE (CM)
2.5V p-p
CM
= 1.25V
= 3.75V
MIN
CM
MAX
V
IN+
Figure 30. Examples of the Analog Inputs to VIN+ and VIN– for
Different Values of VREF for VDD = 5 V
0
T
V
= 25°C
Analog Input Structure
A
= 5V
DD
Figure 31 shows the equivalent circuit of the analog input
structure of the AD7440/AD7450A. The four diodes provide
ESD protection for the analog inputs. Care must be taken to
ensure that the analog input signals never exceed the supply
rails by more than 300 mV. This causes these diodes to become
forward biased and start conducting into the substrate. These
diodes can conduct up to 10 mA without causing irreversible
damage to the part. The capacitors, C1 in Figure 31, are typically
4 pF and can primarily be attributed to pin capacitance. The
resistors are lumped components made up of the on resistance
of the switches. The value of these resistors is typically about
100 Ω. The capacitors, C2, are the ADC’s sampling capacitors
and have a capacitance of 16 pF typically.
–20
–40
R
= 1kΩ
IN
R
= 510Ω
IN
–60
–80
R
= 300Ω
IN
R
= 10
Ω
IN
–100
10
100
1000
INPUT FREQUENCY (kHz)
Figure 32. THD vs. Analog Input Frequency for Various Source Impedances
for VDD=5V
Figure 33 shows a graph of the THD versus the analog input
frequency for VDD of 5 V 5% and 3 V + 20%/–10%, while
sampling at 1 MSPS with an SCLK of 18 MHz. In this case, the
source impedance is 10 Ω.
V
DD
D
D
C2
R1
V
IN+
C1
–50
T
= 25°C
A
–55
–60
–65
–70
–75
–80
–85
–90
V
DD
V
= 2.7V
DD
D
D
C2
R1
V
= 3.6V
DD
V
IN–
C1
Figure 31. Equivalent Analog Input Circuit
Conversion Phase–Switches Open; Track Phase–Switches Closed
V
= 5.25V
DD
V
= 4.75V
DD
10
100
INPUT FREQUENCY (kHz)
1000
Figure 33. THD vs. Analog Input Frequency for 3 V and 5 V Supply Voltages
Rev. B | Page 17 of 28
AD7440/AD7450A
of switched capacitance on the front end of the ADCs. The RC
low-pass filter on each analog input is recommended in ac
applications to remove high frequency components of the
analog input. The architecture of the AD8138 results in outputs
that are very highly balanced over a wide frequency range
without requiring tightly matched external components.
DRIVING DIFFERENTIAL INPUTS
Differential operation requires VIN+ and VIN– to be driven
simultaneously with two equal signals that are 180° out of
phase. The common mode must be set up externally and has a
range determined by VREF, the power supply, and the particular
amplifier used to drive the analog inputs (see Figure 28 and
Figure 29). Differential modes of operation with either an ac or
dc input provide the best THD performance over a wide
frequency range. Because not all applications have a signal
preconditioned for differential operation, there is often a need
to perform single-ended-to-differential conversion.
If the analog input source being used has zero impedance, all
four resistors (RG1, RG2, RF1, and RF2) should be the same. If
the source has a 50 Ω impedance and a 50 Ω termination, for
example, the value of RG2 should be increased by 25 Ω to
balance this parallel impedance on the input and thus ensure
that both the positive and negative analog inputs have the same
gain (see Figure 34). The outputs of the amplifier are perfectly
matched, balanced differential outputs of identical amplitude
and are exactly 180° out of phase.
Differential Amplifier
An ideal method of applying differential drive to the
AD7440/AD7450A is to use a differential amplifier such as the
AD8138. This part can be used as a single-ended-to-differential
amplifier or as a differential-to-differential amplifier. In both
cases, the analog input needs to be bipolar. It also provides
common-mode level shifting and buffering of the bipolar input
signal. Figure 34 shows how the AD8138 can be used as a
single-ended-to-differential amplifier. The positive and negative
outputs of the AD8138 are connected to the respective inputs
on the ADC via a pair of series resistors to minimize the effects
The AD8138 is specified with +3 V, +5 V, and 5 V power
supplies, but the best results are obtained with a 5 V supply.
The AD8132 is a lower cost device that could also be used in
this configuration with slight differences in characteristics to
the AD8138 but with similar performance and operation.
3.75V
2.5V
1.25V
R 1
F
R *
S
R
1
G
V
V
IN+
C*
C*
V
R
OCM
2
AD7440/
AD7450A
+2.5V
GND
–2.5V
AD8138
51Ω
G
R *
S
IN–
V
REF
3.75V
2.5V
R 2
F
1.25V
*MOUNT AS CLOSE TO THE AD7440/AD7450A AS POSSIBLE
AND ENSURE HIGH PRECISION R AND C ARE USED.
S
S
EXTERNAL
(2.5V)
R –50Ω; C–1nF
V
S
REF
R
1 = R 1 = R 2 = 499Ω; R 2 = 523Ω
G
F F G
Figure 34. Using the AD8138 as a Single-Ended-to-Differential Amplifier
Rev. B | Page 18 of 28
AD7440/AD7450A
220Ω
V+
Op Amp Pair
2
×
V
p-p
REF
An op amp pair can be used to directly couple a differential
signal to the AD7440/AD7450A. The circuit configurations
shown in Figure 35 and Figure 36 show how a dual op amp can
be used to convert a single-ended signal into a differential
signal for both a bipolar and unipolar input signal, respectively.
390Ω
220Ω
V
DD
GND
27Ω
V–
220Ω
220Ω
V
V
IN+
AD7440/
AD7450A
IN–
V
REF
V+
The voltage applied to Point A sets up the common-mode
voltage. In both diagrams, it is connected in some way to the
reference, but any value in the common-mode range can be
input here to set up the common mode. The AD8022 is a
suitable dual op amp that could be used in this configuration
to provide differential drive to the AD7440/AD7450A.
A
27Ω
0.1µF
V–
10kΩ
20kΩ
EXTERNAL
V
REF
Figure 36. Dual Op Amp Circuit to Convert a Single-Ended Bipolar Signal into
a Differential Signal
Take care when choosing the op amp; the selection depends on
the required power supply and system performance objectives.
The driver circuits in Figure 35 and Figure 36 are optimized for
dc coupling applications requiring best distortion performance.
RF Transformer
An RF transformer with a center tap offers a good solution for
generating differential inputs in systems that do not need to
be dc-coupled. Figure 37 shows how a transformer is used for
single-ended-to-differential conversion. It provides the benefits
of operating the ADC in the differential mode without contri-
buting additional noise and distortion. An RF transformer also
has the benefit of providing electrical isolation between the
signal source and the ADC. A transformer can be used for most
ac applications. The center tap is used to shift the differential
signal to the common-mode level required; in this case, it is
connected to the reference so the common-mode level is the
value of the reference.
The circuit configuration shown in Figure 35 converts a
unipolar, single-ended signal into a differential signal.
The differential op amp driver circuit in Figure 36 is configured
to convert and level shift a single-ended, ground-referenced
(bipolar) signal to a differential signal centered at the VREF level
of the ADC.
220Ω
2
×
V
p-p
REF
V+
390Ω
V
DD
V
REF
27Ω
GND
3.75V
2.5V
1.25V
V–
V
V
IN+
IN–
220Ω
220Ω
V+
R
R
R
AD7440/
V
AD7450A
IN+
V
AD7440/
AD7450A
REF
C
V
IN–
V
REF
27Ω
A
0.1µF
V–
3.75V
2.5V
1.25V
10kΩ
EXTERNAL
V
REF
EXTERNAL
V
REF
Figure 35. Dual Op Amp Circuit to Convert a Single-Ended Unipolar Signal
into a Differential Signal
Figure 37. Using an RF Transformer to Generate Differential Inputs
Rev. B | Page 19 of 28
AD7440/AD7450A
These examples show that the maximum reference applied to
the AD7440/AD7450A is directly dependent on the value
DIGITAL INPUTS
The digital inputs applied to the device are not limited by the
maximum ratings, which limit the analog limits. Instead the
applied to VDD
.
CS
digital inputs applied,
and SCLK, can go to 7 V and are not
The value of the reference sets the analog input span and the
common-mode voltage range. Errors in the reference source
result in gain errors in the AD7440/AD7450A transfer function
and add to specified full-scale errors on the part. A 0.1 µF
capacitor should be used to decouple the VREF pin to GND.
restricted by the VDD + 0.3 V limits as on the analog input.
The main advantage of the inputs not being restricted to the
VDD + 0.3 V limit is that power supply sequencing issues are
CS
avoided. If
and SCLK are applied before VDD, there is no risk
of latch-up as there would be on the analog inputs if a signal
Figure 38 shows a typical connection diagram for the VREF pin.
Table 6 lists examples of suitable voltage references.
greater than 0.3 V was applied prior to VDD
.
V
REFERENCE
DD
AD7440/
An external reference source is required to supply the reference
to the device. This reference input can range from 100 mV to
3.5 V. With a 5 V power supply, the specified reference is 2.5 V
and the maximum reference is 3.5 V. With a 3 V power supply,
the specified reference is 2 V and the maximum reference is
2.2 V. In both cases, the reference is functional from 100 mV.
AD7450A*
AD780
V
REF
NC
1
2
3
4
OPSEL
8
7
6
5
NC
NC
V
V
DD
IN
2.5V
TEMP
GND
V
OUT
0.1µF
10nF
0.1µF
0.1µF
TRIM
NC
NC = NO CONNECT
Ensure that, when choosing the reference value for a particular
application, the maximum analog input range (VIN max) is
never greater than VDD + 0.3 V to comply with the maximum
ratings of the device. The following two examples calculate the
maximum VREF input that can be used when operating the
AD7440/AD7450A at a VDD of 5 V and 3 V, respectively.
*ADDITIONAL PINS OMITTED FOR CLARITY
Figure 38. Typical VREF Connection Diagram for VDD = 5 V
Table 6. Examples of Suitable Voltage References
Output
Voltage (V)
Initial
Accuracy (%)
Operating
Current (µA)
Reference
AD780
ADR421
ADR420
Example 1
2.5/3
2.5
2.048
0.04
0.04
0.05
1000
500
500
VIN max = VDD + 0.3
VIN max = VREF + VREF/2
If VDD = 5 V, then VIN max = 5.3 V.
SINGLE-ENDED OPERATION
Therefore
When supplied with a 5 V power supply, the AD7440/AD7450A
can handle a single-ended input. The design of these devices is
optimized for differential operation, so with a single-ended
input, performance degrades. Linearity degrades by typically
0.2 LSB, the full-scale errors degrade typically by 1 LSB, and ac
performance is not guaranteed.
3 × VREF/2 = 5.3 V
VREF max = 3.5 V
Thus, when operating at VDD = 5 V, the value of VREF can range
from 100 mV to a maximum value of 3.5 V. When VDD = 4.75 V,
VREF max = 3.17 V.
Example 2
To operate the AD7440/AD7450A in single-ended mode, the
VIN+ input is coupled to the signal source, while the VIN– input is
biased to the appropriate voltage corresponding to the midscale
code transition. This voltage is the common mode, which is a
fixed dc voltage (usually the reference). The VIN+ input swings
around this value and should have a voltage span of 2 × VREF to
make use of the full dynamic range of the part. The input signal
therefore has peak-to-peak values of common mode VREF. If
the analog input is unipolar, an op amp in a noninverting unity
gain configuration can be used to drive the VIN+ pin. The ADC
operates from a single supply, so it is necessary to level shift
ground-based bipolar signals to comply with the input
VIN max = VDD + 0.3
VIN max = VREF + VREF/2
If VDD = 3 V, then VIN max = 3.3 V.
Therefore,
3 × VREF/2 = 3.3 V
V
REF max = 2.2 V
Thus, when operating at VDD = 3 V, the value of VREF can range
from 100 mV to a maximum value of 2.2 V. When VDD = 2.7 V,
VREF max = 2 V.
requirements. An op amp can be configured to rescale and level
shift the ground-based bipolar signal, so it is compatible with
the selected input range of the AD7440/AD7450A (Figure 39).
Rev. B | Page 20 of 28
AD7440/AD7450A
5V
2.5V
0V
R
The conversion result from the AD7440/AD7450A is provided
on the SDATA output as a serial data stream. The bits are
clocked out on the falling edge of the SCLK input. The data
stream of the AD7450A consists of four leading zeros followed
by 12 bits of conversion data provided MSB first; the data
stream of the AD7440 consists of four leading zeros, followed by
the 10 bits of conversion data followed by two trailing zeros,
which is also provided MSB first. In both cases, the output
coding is twos complement.
+2.5V
0V
–2.5V
R
R
V
IN
V
V
IN+
AD7440/
AD7450A
R
V
IN–
REF
0.1µF
EXTERNAL
(2.5V)
V
REF
Sixteen serial clock cycles are required to perform a conversion
Figure 39. Applying a Bipolar Single-Ended Input to the AD7440/AD7450A
CS
and access data from the AD7440/AD7450A.
going low
SERIAL INTERFACE
provides the first leading zero to be read in by the DSP or
microcontroller. The remaining data is then clocked out on the
subsequent SCLK falling edges beginning with the second
leading zero. Thus, the first falling clock edge on the serial clock
provides the second leading zero. The final bit in the data
transfer is valid on the 16th falling edge, having been clocked
out on the previous (15th) falling edge. Once the conversion is
complete and the data has been accessed after the 16 clock
cycles, it is important to ensure that before the next conversion
is initiated, enough time is left to meet the acquisition and
quiet time specifications (see Timing Examples 1 and 2). To
achieve 1 MSPS with an 18 MHz clock for VDD = 3 V and 5 V, an
18-clock burst performs the conversion and leaves enough time
before the next conversion for the acquisition and quiet time.
Figure 2 and Figure 3 show detailed timing diagrams for the
serial interface of the AD7450A and the AD7440, respectively.
The serial clock provides the conversion clock and also controls
CS
the transfer of data from the devices during conversion.
initiates the conversion process and frames the data transfer.
CS
The falling edge of
puts the track-and-hold into hold mode
and takes the bus out of three-state. The analog input is sampled
and the conversion is initiated at this point. The conversion
requires 16 SCLK cycles to complete.
Once 13 SCLK falling edges have occurred, the track-and-hold
goes back into track on the next SCLK rising edge, as shown at
Point B in Figure 2 and Figure 3. On the 16th SCLK falling edge,
the SDATA line goes back into three-state. If the rising edge of
In applications with a slower SCLK, it may be possible to read in
data on each SCLK rising edge; that is, the first rising edge of
CS
occurs before 16 SCLKs have elapsed, the conversion
terminates and the SDATA line goes back into three-state.
CS
SCLK after the
falling edge would have the leading zero
provided and the 15th SCLK edge would have DB0 provided.
CS
10ns
t2
tCONVERT
t5
B
C
1
2
3
4
5
13
14
t6
15
16
SCLK
t8
tQUIET
12.5(1/F
)
tACQUISITION
SCLK
1/THROUGHPUT
Figure 40. Serial Interface Timing Example
Rev. B | Page 21 of 28
AD7440/AD7450A
Timing Example 1
Timing Example 2
Having FSCLK = 18 MHz and a throughput rate of 1 MSPS gives a
cycle time of
Having FSCLK = 5 MHz and a throughput rate of 315 kSPS gives a
cycle time of
1/Throughput = 1/1,000,000 = 1 µs
A cycle consists of
1/Throughput = 1/315,000 = 3.174 µs
A cycle consists of
t2 + 12.5(1/FSCLK) + tACQ = 1 µs
Therefore, if t2 = 10 ns
t2 + 12.5(1/FSCLK) + tACQ = 3.174 µs
Therefore, if t2 is 10 ns
10 ns + 12.5(1/18 MHz) + tACQ = 1 µs
10 ns + 12.5(1/5 MHz) + tACQ = 3.174 µs
t
ACQ = 296 ns
tACQ = 664 ns
This 296 ns satisfies the requirement of 290 ns for tACQ
.
This 664 ns satisfies the requirement of 290 ns for tACQ
.
From Figure 40, tACQ comprises
From Figure 40, tACQ comprises
2.5(1/FSCLK) + t8 + tQUIET
2.5(1/FSCLK) + t8 + tQUIET
where t8 = 35 ns. This allows a value of 122 ns for tQUIET
satisfying the minimum requirement of 60 ns.
,
where t8 = 35 ns. This allows a value of 129 ns for tQUIET,
satisfying the minimum requirement of 60 ns.
As in this example and with other slower clock values, the signal
may already be acquired before the conversion is complete, but
it is still necessary to leave 60 ns minimum tQUIET between
conversions. In Timing Example 2, the signal should be fully
acquired at approximately Point C in Figure 40.
Rev. B | Page 22 of 28
AD7440/AD7450A
MODES OF OPERATION
The operational mode of the AD7440/AD7450A is selected by
POWER-DOWN MODE
CS
controlling the logic state of the signal during a conversion.
This mode is intended for use in applications where slower
throughput rates are required; either the ADC is powered down
between each conversion, or a series of conversions may be
performed at a high throughput rate and the ADC is then
powered down for a relatively long duration between these
bursts of conversions. When the AD7440/AD7450A are in the
power-down mode, all analog circuitry is powered down. To
enter power-down mode, the conversion process must be
There are two possible modes of operation, normal and power
CS
down. The point at which is pulled high after the conversion
has been initiated determines whether or not the device enters
CS
power-down mode. Similarly, if already in power-down,
controls whether the devices return to normal operation or
remain in power-down. These modes of operation are designed
to provide flexible power management options. These options
can be chosen to optimize the power dissipation/throughput
rate ratio for differing application requirements.
CS
interrupted by bringing high anywhere after the second
falling edge of SCLK and before the 10th falling edge of SCLK,
as shown in Figure 42.
NORMAL MODE
This mode is intended for fastest throughput rate performance.
The user does not have to worry about any power-up times with
the AD7440/AD7450A remaining fully powered up all the time.
Figure 41 shows the general diagram of the operation of the
AD7440/AD7450A in this mode. The conversion is initiated on
CS
1
2
10
SCLK
THREE-STATE
SDATA
CS
the falling edge of , as described in the Serial Interface
CS
section. To ensure the part remains fully powered up, must
Figure 42. Entering Power-Down Mode
remain low until at least 10 SCLK falling edges have elapsed
CS
Once has been brought high in this window of SCLKs, the
part enters power-down, the conversion that was initiated by
CS
after the falling edge of
.
CS
the falling edge of is terminated, and SDATA goes back into
CS
three-state. The time from the rising edge of
to SDATA
CS
three-state enabled is never greater than t8 (refer to the Timing
1
10
16
SCLK
CS
Specifications). If is brought high before the second SCLK
falling edge, the part remains in normal mode and does not
power down. This avoids accidental power-down due to glitches
SDATA
4 LEADING ZEROS + CONVERSION RESULT
CS
on the line.
Figure 41. Normal Mode Operation
In order to exit this mode of operation and power up the
AD7440/AD7450A again, a dummy conversion is performed.
CS
If is brought high any time after the 10th SCLK falling edge,
but before the 16th SCLK falling edge, the part remains
powered up but the conversion terminates and SDATA goes
back into three-state. Sixteen serial clock cycles are required to
complete the conversion and access the complete conversion
CS
On the falling edge of , the device begins to power up and
CS
continues to power up as long as is held low until after the
falling edge of the 10th SCLK. The device is fully powered up
after 1 µs has elapsed and, as shown in Figure 43, valid data
results from the next conversion.
CS
result. may idle high until the next conversion or may idle
low until sometime prior to the next conversion. Once a data
transfer is complete, when SDATA has returned to three-state,
another conversion can be initiated after the quiet time, tQUIET
,
CS
has elapsed by again bringing low.
tPOWER-UP
PART BEGINS
TO POWER UP
THIS PART IS FULLY POWERED
UP WITH V FULLY ACQUIRED
IN
CS
A
1
10
16
1
10
16
SCLK
SDATA
INVALID DATA
VALID DATA
Figure 43. Exiting Power-Down Mode
Rev. B | Page 23 of 28
AD7440/AD7450A
CS
Once supplies are applied to the AD7440/AD7450A, the power-
up time is the same as that when powering up from power-
down mode. It takes about 1 µs to power up fully if the part
powers up in normal mode. It is not necessary to wait 1 µs
before executing a dummy cycle to ensure the desired mode of
operation. Instead, the dummy cycle can occur directly after
power is supplied to the ADC. If the first valid conversion is
then performed directly after the dummy conversion, ensure
that adequate acquisition time has been allowed.
If
AD7440/AD7450A again goes back into power-down. This
CS
is brought high before the 10th falling edge of SCLK, the
avoids accidental power-up due to glitches on the
line or an
is low. So
although the device may begin to power up on the falling edge
CS
inadvertent burst of eight SCLK cycles while
CS
CS
of , it again powers down on the rising edge of
as long as
it occurs before the 10th SCLK falling edge.
POWER-UP TIME
The power-up time of the AD7440/AD7450A is typically 1 µs,
which means that with any frequency of SCLK up to 18 MHz,
one dummy cycle is always sufficient to allow the device to
power up. Once the dummy cycle is complete, the ADC is fully
powered up and the input signal is acquired properly. The quiet
time, tQUIET, must still be allowed from the point at which the
bus goes back into three-state after the dummy conversion to
As mentioned earlier, when powering up from the power-down
mode, the part returns to track mode upon the first SCLK edge
CS
applied after the falling edge of . However, when the ADC
powers up initially after supplies are applied, the track-and-hold
is already in track mode. Assuming the user has the facility to
monitor the ADC supply current, this means the ADC powers
up in the desired mode of operation, and thus a dummy cycle is
not required to change mode. A dummy cycle is therefore not
required to place the track-and-hold into track mode.
CS
the next falling edge of
.
When running at the maximum throughput rate of 1 MSPS, the
AD7440/AD7450A power up and acquire a signal within
0.5 LSB in one dummy cycle, 1 µs. When powering up from
the power-down mode with a dummy cycle, as in Figure 43, the
track-and-hold, which was in hold mode while the part was
powered down, returns to track mode after the first SCLK edge
POWER VS. THROUGHPUT RATE
By using the power-down mode on the AD7440/AD7450A
when not converting, the average power consumption of the
ADC decreases at lower throughput rates. Figure 44 shows how,
as the throughput rate is reduced, the device remains in its
power-down state longer and the average power consumption is
reduced accordingly for both 5 V and 3 V power supplies.
CS
the part receives after the falling edge of . This is shown as
Point A in Figure 43.
Although at any SCLK frequency one dummy cycle is sufficient
to power up the device and acquire VIN, it does not mean that a
full dummy cycle of 16 SCLKs must always elapse to power up
the device and acquire VIN fully; 1 µs is sufficient to power up
the device and acquire the input signal.
For example, if the AD7440/AD7450A are operated in
continuous sampling mode with a throughput rate of 100 kSPS
and an SCLK of 18 MHz, and the device is placed in power-
down mode between conversions, the power consumption is
calculated as follows:
For example, if a 5 MHz SCLK frequency was applied to the
ADC, the cycle time would be 3.2 µs (1/(5 MHz) ×16). In one
dummy cycle, 3.2 µs, the part would be powered up and VIN
acquired fully. However, after 1 µs with a 5 MHz SCLK, only five
SCLK cycles would have elapsed. At this stage, the ADC would
be fully powered up and the signal acquired. So in this case, the
Power Dissipation during Normal Operation = 9.25 mW max
(for VDD = 5 V)
If the power-up time is one dummy cycle (1 µs), and the
remaining conversion time is another cycle (1 µs), the
AD7440/AD7450A can be said to dissipate 9.25 mW for 2 µs1
during each conversion cycle.
CS
can be brought high after the 10th SCLK falling edge and
brought low again after a time, tQUIET, to initiate the conversion.
If the throughput rate = 100 kSPS, the cycle time = 10 µs and
the average power dissipated during each cycle is
(2/10) × 9.25mW = 1.85 mW.
When power supplies are first applied to the device, the ADC
may power up in either power-down mode or normal mode.
Because of this, it is best to allow a dummy cycle to elapse to
ensure the part is fully powered up before attempting a valid
conversion. Likewise, if the user wants the part to power up in
power-down mode, the dummy cycle may be used to ensure the
device is in power-down by executing a cycle such as the one
shown in Figure 42.
For the same scenario, if VDD = 3 V, the power dissipation during
normal operation is 4 mW max.
The AD7440/AD7450A can now be said to dissipate 4 mW for
2 µs1 during each conversion cycle.
1This figure assumes a very short time to enter power-down mode. This
increases as the burst of clocks used to enter this mode is increased.
Rev. B | Page 24 of 28
AD7440/AD7450A
Thus, the average power dissipated during each cycle with a
throughput rate of 100 kSPS is (2/10) × 4 mW = 0.8 mW.
The connection diagram is shown in Figure 45. The ADSP-21xx
has the TFS and RFS of the SPORT tied together, with TFS set
as an output and RFS set as an input. The DSP operates in
alternate framing mode and the SPORT control register is set
up as described. The frame synchronization signal generated on
This is how the power numbers in Figure 44 are calculated.
For throughput rates above 320 kSPS, it is recommended to
reduce the serial clock frequency for best power performance.
CS
the TFS is tied to
and, as with all signal processing
applications, equidistant sampling is necessary. However in this
example, the timer interrupt is used to control the sampling rate
of the ADC; under certain conditions, equidistant sampling may
not be achieved.
100
V
= 5V
DD
10
1
The timer registers, for example, are loaded with a value that
provides an interrupt at the required sample interval. When an
interrupt is received, a value is transmitted with TFS/DT (ADC
control word). The TFS is used to control the RFS and therefore
the reading of data. The frequency of the serial clock is set in
the SCLKDIV register. When the instruction to transmit with
TFS is given (AX0 = TX0), the state of the SCLK is checked. The
DSP waits until the SCLK has gone high, low, and high again
before starting transmission. If the timer and SCLK values are
chosen such that the instruction to transmit occurs on or near
the rising edge of SCLK, then the data may be transmitted or it
may wait until the next clock edge.
V
= 3V
DD
0.1
0.01
0
50
100
150
200
250
300
350
THROUGHPUT (kSPS)
Figure 44. Power vs. Throughput Rate for Power-Down Mode
MICROPROCESSOR AND DSP INTERFACING
ADSP-21xx*
AD7440/
AD7450A*
The serial interface on the AD7440/AD7450A allows the parts
to be directly connected to many different microprocessors.
This section explains how to interface the AD7440/AD7450A
with some of the more common microcontroller and DSP serial
interface protocols.
SCLK
SDATA
CS
SCLK
DR
RFS
TFS
AD7440/AD7450A to ADSP-21xx
The ADSP-21xx family of DSPs is interfaced directly to the
AD7440/AD7450A without any glue logic required.
*ADDITIONAL PINS REMOVED FOR CLARITY
Figure 45. Interfacing to the ADSP-21xx
The SPORT control register should be set up as follows:
For example, the ADSP-2111 has a master clock frequency of
16 MHz. If the SCLKDIV register is loaded with the value 3, an
SCLK of 2 MHz is obtained and eight master clock periods
elapse for every SCLK period. If the timer registers are loaded
with the value 803, then 100.5 SCLKs occur between interrupts
and subsequently between transmit instructions. This situation
results in nonequidistant sampling as the transmit instruction is
occurring on a SCLK edge. If the number of SCLKs between
interrupts is a whole integer figure of N, equidistant sampling is
implemented by the DSP.
TFSW = RFSW = 1
INVRFS = INVTFS = 1
DTYPE = 00
Alternate framing
Active low frame signal
Right-justify data
16-bit data-words
Internal serial clock
Frame every word
SLEN = 1111
ISCLK = 1
TFSR = RFSR = 1
IRFS = 0
ITFS = 1
To implement power-down mode, SLEN should be set to 1001
to issue an 8-bit SCLK burst.
Rev. B | Page 25 of 28
AD7440/AD7450A
AD7440/AD7450A to TMS320C5x/C54x
GROUNDING AND LAYOUT HINTS
The serial interface on the TMS320C5x/C54x uses a continuous
serial clock and frame synchronization signals to synchronize
the data transfer operations with peripheral devices like the
The printed circuit board that houses the AD7440/AD7450A
should be designed so that the analog and digital sections are
separated and confined to certain areas of the board. This
facilitates the use of ground planes that can be easily separated.
A minimum etch technique is generally best for ground planes
as it gives the best shielding. Digital and analog ground planes
should be joined in only one place, a star ground point
established as close to the GND pin on the AD7440/AD7450A
as possible. Avoid running digital lines under the devices
because this couples noise onto the die. The analog ground
plane should be allowed to run under the AD7440/AD7450A to
avoid noise coupling. The power supply lines to the
CS
AD7440/AD7450A. The
input allows easy interfacing
between the TMS320C5x/C54x and the AD7440/AD7450A
without any glue logic required. The serial port of the
TMS320C5x/C54x is set up to operate in burst mode with
internal CLKx (Tx serial clock) and FSx (Tx frame sync). The
serial port control register (SPC) must have the following setup:
FO = 0, FSM = 1, MCM = 1, and TxM = 1. The format bit, FO,
may be set to 1 to set the word length to eight bits in order to
implement the power-down mode on the AD7440/AD7450A.
The connection diagram is shown in Figure 46. For signal
processing applications, it is imperative that the frame
synchronization signal from the TMS320C5x/C54x provide
equidistant sampling.
AD7440/AD7450A should use as large a trace as possible to
provide low impedance paths and reduce the effects of glitches
on the power supply line.
Fast switching signals like clocks should be shielded with digital
ground to avoid radiating noise to other sections of the board,
and clock signals should never run near the analog inputs.
Avoid crossover of digital and analog signals. Traces on opposite
sides of the board should run at right angles to each other. This
reduces the effects of feedthrough through the board. A micro-
strip technique is by far the best but is not always possible with
a double-sided board.
TMS320C5x/
AD7440/
C54x*
AD7450A*
SCLK
CLKx
CLKR
DR
SDATA
CS
FSx
FSR
*ADDITIONAL PINS REMOVED FOR CLARITY
In this technique, the component side of the board is dedicated
to ground planes while signals are placed on the solder side.
Good decoupling is also important. All analog supplies should
be decoupled with 10 µF tantalum capacitors in parallel with
0.1 µF capacitors to GND. To achieve the best from these
decoupling components, they must be placed as close as
possible to the device.
Figure 46. Interfacing to the TMS320C5x/C54
AD7440/AD7450A to DSP56xxx
The connection diagram in Figure 47 shows how the device can
be connected to the synchronous serial interface (SSI) of the
DSP56xxx family of DSPs from Motorola. The SSI is operated in
synchronous mode (SYN bit in CRB = 1) with internally
generated 1-word frame sync for both Tx and Rx (Bits FSL1 = 0
and FSL0 = 0 in CRB). Set the word length to 16 by setting Bits
WL1 = 1 and WL0 = 0 in CRA. To implement power-down
mode on the AD7440/AD7450A, the word length can be
changed to 8 bits by setting Bits WL1 = 0 and WL0 = 0 in CRA.
For signal processing applications, it is imperative that the
frame synchronization signal from the DSP56xxx provide
equidistant sampling.
EVALUATING THE AD7440/AD7450A
PERFORMANCE
The evaluation board package includes a fully assembled and
tested evaluation board, documentation, and software for
controlling the board from a PC via the evaluation board
controller. The evaluation board controller can be used in
conjunction with the AD7440/AD7450A evaluation board, as
well as many other Analog Devices evaluation boards ending
with the CB designator, to demonstrate and evaluate the ac and
dc performance of the AD7440/AD7450A.
AD7440/
AD7450A*
DSP56xxx*
The software allows the user to perform ac (fast Fourier
transform) and dc (histogram of codes) tests on the device. See
the AD7440/AD7450A application note that accompanies the
evaluation kit for more information.
SCLK
SCLK
SDATA
CS
SRD
SR2
*ADDITIONAL PINS REMOVED FOR CLARITY
Figure 47. Interfacing to the DSP56xxx
Rev. B | Page 26 of 28
AD7440/AD7450A
OUTLINE DIMENSIONS
2.90 BSC
8
1
7
2
6
3
5
4
1.60 BSC
PIN 1
2.80 BSC
0.65 BSC
1.95
BSC
1.30
1.15
0.90
1.45 MAX
0.22
0.08
0.60
0.45
0.30
8°
4°
0°
0.38
0.22
0.15 MAX
SEATING
PLANE
COMPLIANT TO JEDEC STANDARDS MO-178BA
Figure 48. 8-Lead Small Outline Transistor Package [SOT-23]
(RT-8)
Dimensions shown in millimeters
3.00
BSC
8
5
4
4.90
BSC
3.00
BSC
PIN 1
0.65 BSC
1.10 MAX
0.15
0.00
0.80
0.60
0.40
8°
0°
0.38
0.22
0.23
0.08
COPLANARITY
0.10
SEATING
PLANE
COMPLIANT TO JEDEC STANDARDS MO-187AA
Figure 49. 8-Lead Mini Small Outline Package [MSOP]
(RM-8)
Dimensions shown in millimeters
Rev. B | Page 27 of 28
AD7440/AD7450A
ORDERING GUIDE
Model
Temperature Range
–40°C to +85°C
–40°C to +85°C
–40°C to +85°C
–40°C to +85°C
–40°C to +85°C
–40°C to +85°C
–40°C to +85°C
–40°C to +85°C
Linearity Error (LSB)1
Package Option2
RT-8
RT-8
RM-8
RM-8
RT-8
RT-8
RM-8
Branding
CTB
CTB
CTB
CTB
CSB
CSB
CSB
CSB
AD7440BRT-REEL7
AD7440BRT-R2
AD7440BRM
±0.5
±0.5
±0.5
±0.5
±±
±±
±±
±±
AD7440BRM-REEL7
AD7450ABRT-REEL7
AD7450ABRT-R2
AD7450ABRM
AD7450ABRM-REEL7
EVAL-AD7440CB3
EVAL-AD7450ACB3
EVAL-CONTROL BRD24
RM-8
Evaluation Board
Evaluation Board
Controller Board
± Linearity error here refers to integral nonlinearity error.
2 RT = SOT-23; RM = MSOP
3 This can be used as a standalone evaluation board or in conjunction with the evaluation board controller for evaluation/demonstration purposes.
4 Evaluation board controller. This board is a complete unit allowing a PC to control and communicate with all Analog Devices’ evaluation boards ending in the CB
designator. For a complete evaluation kit, order the ADC evaluation board (that is, the EVAL-AD7450ACB or EVAL-AD7440CB), the EVAL-CONTROL BRD2, and a ±2 V ac
transformer. See the AD7440/AD7450A application note that accompanies the evaluation kit for more information.
©2004 Analog Devices, Inc. All rights reserved. Trademarks and
registered trademarks are the property of their respective owners.
C03051-0-2/04(B)
Rev. B | Page 28 of 28
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