概述
数据手册
替代型号AD7468BRMZ-REEL7 概述
1.6 V, Micropower 12-/10-/8-Bit ADCs 1.6 V，微功耗12位/ 10位/ 8位ADC
AD7468BRMZ-REEL7 数据手册
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AD7466/AD7467/AD7468
FEATURES
FUNCTIONAL BLOCK DIAGRAM
V
DD
Specified for VDD of 1.6 V to 3.6 V
Low power:
0.62 mW typical at 100 kSPS with 3 V supplies
0.48 mW typical at 50 kSPS with 3.6 V supplies
0.12 mW typical at 100 kSPS with 1.6 V supplies
Fast throughput rate: 200 kSPS
Wide input bandwidth:
71 dB SNR at 30 kHz input frequency
Flexible power/serial clock speed management
No pipeline delays
12-/10-/8-BIT
SUCCESSIVE
APPROXIMATION
ADC
T/H
V
IN
SCLK
SDATA
CS
CONTROL
LOGIC
High speed serial interface:
AD7466/AD7467/AD7468
SPI/QSPI™/MICROWIRE™/DSP compatible
Automatic power-down
GND
Power-down mode: 8 nA typical
6-lead SOT-23 package
Figure 1.
8-lead MSOP package
APPLICATIONS
Battery-powered systems
Medical instruments
Remote data acquisition
Isolated data acquisition
GENERAL DESCRIPTION
PRODUCT HIGHLIGHTS
The AD7466/AD7467/AD74681 are 12-/10-/8-bit, high speed,
low power, successive approximation analog-to-digital
converters (ADCs), respectively. The parts operate from a single
1.6 V to 3.6 V power supply and feature throughput rates up to
200 kSPS with low power dissipation. The parts contain a low
noise, wide bandwidth track-and-hold amplifier, which can
handle input frequencies in excess of 3 MHz.
1. Specified for supply voltages of 1.6 V to 3.6 V.
2. 12-, 10-, and 8-bit ADCs in SOT-23 and MSOP packages.
3. High throughput rate with low power consumption.
Power consumption in normal mode of operation at
100 kSPS and 3 V is 0.9 mW maximum.
4. Flexible power/serial clock speed management.
The conversion rate is determined by the serial clock,
allowing the conversion time to be reduced through
increases in the serial clock speed. Automatic power-down
after conversion allows the average power consumption to
be reduced when in power-down. Current consumption is
0.1 μA maximum and 8 nA typically when in power-down.
The conversion process and data acquisition are controlled
CS
using
and the serial clock, allowing the devices to interface
with microprocessors or DSPs. The input signal is sampled on
CS
the falling edge of , and the conversion is also initiated at this
point. There are no pipeline delays associated with the part.
The reference for the part is taken internally from VDD. This
allows the widest dynamic input range to the ADC. Thus, the
analog input range for the part is 0 V to VDD. The conversion
rate is determined by the SCLK.
5. Reference derived from the power supply.
6. No pipeline delay.
7. The part features a standard successive approximation
CS
ADC with accurate control of conversions via a
input.
1 Protected by U.S. Patent No. 6,681,332.
Rev. C
Information furnished by Analog Devices is believed to be accurate and reliable. However, no
responsibility is assumed by Analog Devices for its use, nor for any infringements of patents or other
rights of third parties that may result from its use. Specifications subject to change without notice. No
license is granted by implication or otherwise under any patent or patent rights of Analog Devices.
Trademarks and registeredtrademarks arethe property of their respective owners.
One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A.
Tel: 781.329.4700 www.analog.com
Fax: 781.461.3113 ©2003–2007 Analog Devices, Inc. All rights reserved.
AD7466/AD7467/AD7468
TABLE OF CONTENTS
Features .............................................................................................. 1
Power Requirement Curves ...................................................... 13
Terminology.................................................................................... 16
Theory of Operation ...................................................................... 17
Circuit Information.................................................................... 17
Converter Operation.................................................................. 17
ADC Transfer Function............................................................. 17
Typical Connection Diagram ................................................... 17
Analog Input ............................................................................... 18
Digital Inputs .............................................................................. 18
Normal Mode.............................................................................. 19
Power Consumption .................................................................. 20
Serial Interface ................................................................................ 22
Microprocessor Interfacing....................................................... 23
Application Hints ........................................................................... 25
Grounding and Layout .............................................................. 25
Evaluating the Performance of the AD7466 and AD7467.... 25
Outline Dimensions....................................................................... 26
Ordering Guide .......................................................................... 27
Applications....................................................................................... 1
Functional Block Diagram .............................................................. 1
General Description......................................................................... 1
Product Highlights ........................................................................... 1
Revision History ............................................................................... 2
Specifications..................................................................................... 3
AD7466.......................................................................................... 3
AD7467.......................................................................................... 5
AD7468.......................................................................................... 7
Timing Specifications .................................................................. 9
Timing Examples........................................................................ 10
Absolute Maximum Ratings.......................................................... 11
ESD Caution................................................................................ 11
Pin Configurations and Function Descriptions ......................... 12
Typical Performance Characteristics ........................................... 13
Dynamic Performance Curves ................................................. 13
DC Accuracy Curves ................................................................. 13
REVISION HISTORY
5/07—Rev. B to Rev. C
Deleted Figure 3.............................................................................. 10
Updated Outline Dimensions....................................................... 26
Changes to Ordering Guide .......................................................... 27
4/05—Rev. A to Rev. B
Moved Terminology Section......................................................... 16
Changes to Ordering Guide .......................................................... 27
11/04—Rev. 0 to Rev. A
Updated Format..................................................................Universal
Changes to General Description .................................................... 1
Added Patent Number ..................................................................... 1
Updated Outline Dimensions....................................................... 26
Changes to Ordering Guide .......................................................... 27
5/03—Revision 0: Initial Version
Rev. C | Page 2 of 28
AD7466/AD7467/AD7468
SPECIFICATIONS
AD7466
VDD = 1.6 V to 3.6 V, fSCLK = 3.4 MHz, fSAMPLE = 100 kSPS, unless otherwise noted. TA = TMIN to TMAX, unless otherwise noted.
The temperature range for the B version is −40°C to +85°C.
Table 1.
Parameter
B Version
Unit
Test Conditions/Comments
fIN = 30 kHz sine wave
1.8 V ≤ VDD ≤ 2 V; see the Terminology section
2.5 V ≤ VDD ≤ 3.6 V
DYNAMIC PERFORMANCE
Signal-to-Noise and Distortion (SINAD)
69
70
70
70
71
71
70.5
−83
−85
dB min
dB min
dB typ
dB min
dB typ
dB min
dB typ
dB typ
dB typ
VDD = 1.6 V
Signal-to-Noise Ratio (SNR)
1.8 V ≤ VDD ≤ 2 V; see the Terminology section
1.8 V ≤ VDD ≤ 2 V
2.5 V ≤ VDD ≤ 3.6 V
VDD = 1.6 V
See the Terminology section
See the Terminology section
Total Harmonic Distortion (THD)
Peak Harmonic or Spurious Noise (SFDR)
Intermodulation Distortion (IMD)
fa = 29.1 kHz, fb = 29.9 kHz; see the Terminology
section
Second-Order Terms
Third-Order Terms
Aperture Delay
−84
−86
10
dB typ
dB typ
ns typ
Aperture Jitter
40
ps typ
Full Power Bandwidth
3.2
1.9
750
450
MHz typ
MHz typ
kHz typ
kHz typ
@ 3 dB, 2.5 V ≤ VDD ≤ 3.6 V
@ 3 dB, 1.6 V ≤ VDD ≤ 2.2 V
@ 0.1 dB, 2.5 V ≤ VDD ≤ 3.6 V
@ 0.1 dB, 1.6 V ≤ VDD ≤ 2.2 V
DC ACCURACY
Maximum specifications apply as typical figures when
VDD = 1.6 V
Resolution
12
Bits
Integral Nonlinearity
Differential Nonlinearity
1.5
−0.9/+1.5
LSB max
LSB max
See the Terminology section
Guaranteed no missed codes to 12 bits; see the
Terminology section
Offset Error
Gain Error
Total Unadjusted Error (TUE)
ANALOG INPUT
1
1
2
LSB max
LSB max
LSB max
See the Terminology section
See the Terminology section
See the Terminology section
Input Voltage Ranges
DC Leakage Current
Input Capacitance
LOGIC INPUTS
0 to VDD
1
20
V
μA max
pF typ
Input High Voltage, VINH
0.7 × VDD
V min
1.6 V ≤ VDD < 2.7 V
2
V min
2.7 V ≤ VDD ≤ 3.6 V
Input Low Voltage, VINL
0.2 × VDD
0.3 × VDD
0.8
1
1
V max
V max
V max
μA max
μA typ
pF max
1.6 V ≤ VDD < 1.8 V
1.8 V ≤ VDD < 2.7 V
2.7 V ≤ VDD ≤ 3.6 V
Typically 20 nA, VIN = 0 V or VDD
Input Current, IIN, SCLK Pin
Input Current, IIN, CS Pin
Input Capacitance, CIN
10
Sample tested at 25°C to ensure compliance
Rev. C | Page 3 of 28
AD7466/AD7467/AD7468
Parameter
B Version
Unit
Test Conditions/Comments
LOGIC OUTPUTS
Output High Voltage, VOH
Output Low Voltage, VOL
Floating-State Leakage Current
Floating-State Output Capacitance
Output Coding
VDD − 0.2
0.2
1
V min
ISOURCE = 200 μA, VDD = 1.6 V to 3.6 V
ISINK = 200 μA
V max
μA max
pF max
10
Straight (natural)
binary
CONVERSION RATE
Conversion Time
Throughput Rate
POWER REQUIREMENTS
VDD
4.70
200
μs max
kSPS max
16 SCLK cycles with SCLK at 3.4 MHz
See the Serial Interface section
1.6/3.6
V min/max
IDD
Digital inputs = 0 V or VDD
VDD = 3 V, fSAMPLE = 100 kSPS
VDD = 3 V, fSAMPLE = 50 kSPS
VDD = 3 V, fSAMPLE = 10 kSPS
VDD = 2.5 V, fSAMPLE = 100 kSPS
VDD = 2.5 V, fSAMPLE = 50 kSPS
VDD = 2.5 V, fSAMPLE = 10 kSPS
VDD = 1.8 V, fSAMPLE = 100 kSPS
VDD = 1.8 V, fSAMPLE = 50 kSPS
VDD = 1.8 V, fSAMPLE = 10 kSPS
SCLK on or off, typically 8 nA
See the Power Consumption section
VDD = 3 V, fSAMPLE = 100 kSPS
VDD = 2.5 V, fSAMPLE = 100 kSPS
VDD = 1.8 V, fSAMPLE = 100 kSPS
VDD = 3 V
Normal Mode (Operational)
300
110
20
240
80
16
165
50
μA max
μA typ
μA typ
μA max
μA typ
μA typ
μA max
μA typ
μA typ
μA max
10
0.1
Power-Down Mode
Power Dissipation
Normal Mode (Operational)
0.9
0.6
0.3
0.3
mW max
mW max
mW max
μW max
Power-Down Mode
Rev. C | Page 4 of 28
AD7466/AD7467/AD7468
AD7467
VDD = 1.6 V to 3.6 V, fSCLK = 3.4 MHz, fSAMPLE = 100 kSPS, unless otherwise noted. TA = TMIN to TMAX, unless otherwise noted.
The temperature range for the B version is −40°C to +85°C.
Table 2.
Parameter
B Version
Unit
Test Conditions/Comments
DYNAMIC PERFORMANCE
Maximum/minimum specifications apply as typical figures
when VDD = 1.6 V, fIN = 30 kHz sine wave
Signal-to-Noise and Distortion (SINAD)
Total Harmonic Distortion (THD)
Peak Harmonic or Spurious Noise (SFDR) −74
Intermodulation Distortion (IMD)
61
−72
dB min
dB max
dB max
See the Terminology section
See the Terminology section
See the Terminology section
fa = 29.1 kHz, fb = 29.9 kHz; see the Terminology section
Second-Order Terms
Third-Order Terms
Aperture Delay
−83
−83
10
dB typ
dB typ
ns typ
Aperture Jitter
40
ps typ
Full Power Bandwidth
3.2
1.9
750
450
MHz typ
MHz typ
kHz typ
kHz typ
@ 3 dB, 2.5 V ≤ VDD ≤ 3.6 V
@ 3 dB, 1.6 V ≤ VDD ≤ 2.2 V
@ 0.1 dB, 2.5 V ≤ VDD ≤ 3.6 V
@ 0.1 dB, 1.6 V ≤ VDD ≤ 2.2 V
DC ACCURACY
Maximum specifications apply as typical figures when
VDD = 1.6 V
Resolution
10
Bits
Integral Nonlinearity
Differential Nonlinearity
0.5
0.5
LSB max
LSB max
See the Terminology section
Guaranteed no missed codes to 10 bits; see the
Terminology section
Offset Error
Gain Error
Total Unadjusted Error (TUE)
ANALOG INPUT
0.2
0.2
1
LSB max
LSB max
LSB max
See the Terminology section
See the Terminology section
See the Terminology section
Input Voltage Ranges
DC Leakage Current
Input Capacitance
LOGIC INPUTS
0 to VDD
1
20
V
μA max
pF typ
Input High Voltage, VINH
0.7 × VDD
V min
1.6 V ≤ VDD < 2.7 V
2
V min
2.7 V ≤ VDD ≤ 3.6 V
Input Low Voltage, VINL
0.2 × VDD
0.3 × VDD
0.8
1
1
V max
V max
V max
μA max
μA typ
pF max
1.6 V ≤ VDD < 1.8 V
1.8 V ≤V DD < 2.7 V
2.7 V ≤ VDD ≤ 3.6 V
Typically 20 nA, VIN = 0 V or VDD
Input Current, IIN, SCLK Pin
Input Current, IIN, CS Pin
Input Capacitance, CIN
10
Sample tested at 25°C to ensure compliance
LOGIC OUTPUTS
Output High Voltage, VOH
Output Low Voltage, VOL
Floating-State Leakage Current
Floating-State Output Capacitance
Output Coding
VDD − 0.2
0.2
1
V min
ISOURCE = 200 μA, VDD = 1.6 V to 3.6 V
ISINK = 200 μA
V max
μA max
pF max
10
Sample tested at 25°C to ensure compliance
Straight (natural)
binary
CONVERSION RATE
Conversion Time
Throughput Rate
3.52
275
μs max
kSPS max
12 SCLK cycles with SCLK at 3.4 MHz
See the Serial Interface section
Rev. C | Page 5 of 28
AD7466/AD7467/AD7468
Parameter
B Version
Unit
Test Conditions/Comments
POWER REQUIREMENTS
VDD
1.6/3.6
V min/max
IDD
Digital inputs = 0 V or VDD
Normal Mode (Operational)
210
170
140
0.1
μA max
μA max
μA max
μA max
VDD = 3 V, fSAMPLE = 100 kSPS
VDD = 2.5 V, fSAMPLE = 100 kSPS
VDD = 1.8 V, fSAMPLE = 100 kSPS
SCLK on or off, typically 8 nA
See the Power Consumption section
VDD = 3 V, fSAMPLE = 100 kSPS
VDD = 2.5 V, fSAMPLE = 100 kSPS
VDD = 1.8 V, fSAMPLE = 100 kSPS
Power-Down Mode
Power Dissipation
Normal Mode (Operational)
0.63
0.42
0.25
mW max
mW max
mW max
Power-Down Mode
0.3
μW max
VDD = 3 V
Rev. C | Page 6 of 28
AD7466/AD7467/AD7468
AD7468
VDD = 1.6 V to 3.6 V, fSCLK = 3.4 MHz, fSAMPLE = 100 kSPS, unless otherwise noted. TA = TMIN to TMAX, unless otherwise noted.
The temperature range for the B version is −40°C to +85°C.
Table 3.
Parameter
B Version
Unit
Test Conditions/Comments
DYNAMIC PERFORMANCE
Maximum/minimum specifications apply as typical figures
when VDD = 1.6 V, fIN = 30 kHz sine wave
Signal-to-Noise and Distortion (SINAD) 49
dB min
dB max
dB max
See the Terminology section
See the Terminology section
See the Terminology section
Total Harmonic Distortion (THD)
−66
Peak Harmonic or Spurious Noise
(SFDR)
−66
Intermodulation Distortion (IMD)
Second-Order Terms
Third-Order Terms
fa = 29.1 kHz, fb = 29.9 kHz; see the Terminology section
−77
−77
10
dB typ
dB typ
ns typ
Aperture Delay
Aperture Jitter
40
ps typ
Full Power Bandwidth
3.2
1.9
750
450
MHz typ
MHz typ
kHz typ
kHz typ
@ 3 dB, 2.5 V ≤ VDD ≤ 3.6 V
@ 3 dB, 1.6 V ≤ VDD ≤ 2.2 V
@ 0.1 dB, 2.5 V ≤ VDD ≤ 3.6 V
@ 0.1 dB, 1.6 V ≤ VDD ≤ 2.2 V
DC ACCURACY
Maximum specifications apply as typical figures when
VDD = 1.6 V
Resolution
8
Bits
Integral Nonlinearity
Differential Nonlinearity
0.2
0.2
LSB max
LSB max
See the Terminology section
Guaranteed no missed codes to 8 bits; see the Terminology
section
Offset Error
Gain Error
Total Unadjusted Error (TUE)
ANALOG INPUT
0.1
0.1
0.3
LSB max
LSB max
LSB max
See the Terminology section
See the Terminology section
See the Terminology section
Input Voltage Ranges
DC Leakage Current
Input Capacitance
LOGIC INPUTS
0 to VDD
1
20
V
μA max
pF typ
Input High Voltage, VINH
0.7 × VDD
V min
1.6 V ≤ VDD < 2.7 V
2
V min
2.7 V ≤ VDD ≤ 3.6 V
Input Low Voltage, VINL
0.2 × VDD
0.3 × VDD
0.8
1
1
V max
V max
V max
μA max
μA typ
pF max
1.6 V ≤ VDD < 1.8 V
1.8 V ≤ VDD < 2.7 V
2.7 V ≤ VDD ≤ 3.6 V
Typically 20 nA, VIN = 0 V or VDD
Input Current, IIN, SCLK Pin
Input Current, IIN, CS Pin
Input Capacitance, CIN
10
Sample tested at 25°C to ensure compliance
LOGIC OUTPUTS
Output High Voltage, VOH
Output Low Voltage, VOL
Floating-State Leakage Current
Floating-State Output Capacitance
Output Coding
VDD − 0.2
0.2
1
V min
ISOURCE = 200 μA; VDD = 1.6 V to 3.6 V
ISINK = 200 μA
V max
μA max
pF max
10
Sample tested at 25°C to ensure compliance
Straight (natural)
binary
CONVERSION RATE
Conversion Time
Throughput Rate
2.94
320
μs max
kSPS max
10 SCLK cycles with SCLK at 3.4 MHz
See the Serial Interface section
Rev. C | Page 7 of 28
AD7466/AD7467/AD7468
Parameter
B Version
Unit
Test Conditions/Comments
POWER REQUIREMENTS
VDD
1.6/3.6
V min/max
IDD
Digital inputs = 0 V or VDD
VDD = 3 V, fSAMPLE = 100 kSPS
VDD = 2.5 V, fSAMPLE = 100 kSPS
VDD = 1.8 V, fSAMPLE = 100 kSPS
SCLK on or off, typically 8 nA
See the Power Consumption section
VDD = 3 V, fSAMPLE = 100 kSPS
VDD = 2.5 V, fSAMPLE = 100 kSPS
VDD = 1.8 V, fSAMPLE = 100 kSPS
VDD = 3 V
Normal Mode (Operational)
190
155
120
0.1
μA max
μA max
μA max
μA max
Power-Down Mode
Power Dissipation
Normal Mode (Operational)
0.57
0.4
0.2
mW max
mW max
mW max
μW max
Power-Down Mode
0.3
Rev. C | Page 8 of 28
AD7466/AD7467/AD7468
TIMING SPECIFICATIONS
For all devices, VDD = 1.6 V to 3.6 V; TA = TMIN to TMAX, unless otherwise noted. Sample tested at 25°C to ensure compliance. All input
signals are specified with tr = tf = 5 ns (10% to 90% of VDD) and timed from a voltage level of 1.4 V.
Table 4.
Parameter
Limit at TMIN, TMAX
Unit
Description
fSCLK
3.4
10
20
150
MHz max
kHz min
kHz min
kHz min
Mark/space ratio for the SCLK input is 40/60 to 60/40.
1.6 V ≤ VDD ≤ 3 V; minimum fSCLK at which specifications are guaranteed.
VDD = 3.3 V; minimum fSCLK at which specifications are guaranteed.
VDD = 3.6 V; minimum fSCLK at which specifications are guaranteed.
tCONVERT
16 × tSCLK
12 × tSCLK
10 × tSCLK
AD7466.
AD7467.
AD7468.
Acquisition Time
Acquisition time/power-up time from power-down. See the Terminology section.
The acquisition time is the time required for the part to acquire a full-scale step
input value within 1 LSB or a 30 kHz ac input value within 0.5 LSB.
780
640
10
ns max
ns max
ns min
VDD = 1.6 V.
1.8 V ≤ VDD ≤ 3.6 V.
tQUIET
Minimum quiet time required between bus relinquish and the start of the next
conversion.
t1
t2
10
55
ns min
ns min
Minimum CS pulse width.
CS to SCLK setup time. If VDD = 1.6 V and fSCLK = 3.4 MHz, t2 has to be 192 ns
minimum in order to meet the maximum figure for the acquisition time.
t3
t4
55
ns max
ns max
Delay from CS until SDATA is three-state disabled. Measured with the load circuit
in Figure 2 and defined as the time required for the output to cross the VIH or VIL
voltage.
Data access time after SCLK falling edge. Measured with the load circuit in Figure 2
and defined as the time required for the output to cross the VIH or VIL voltage.
140
t5
t6
t7
0.4 tSCLK
0.4 tSCLK
10
ns min
ns min
ns min
SCLK low pulse width.
SCLK high pulse width.
SCLK to data valid hold time. Measured with the load circuit in Figure 2 and
defined as the time required for the output to cross the VIH or VIL voltage.
t8
60
ns max
SCLK falling edge to SDATA three-state. t8 is derived from the measured time taken
by the data outputs to change 0.5 V when loaded with the circuit in Figure 2. The
measured number is then extrapolated back to remove the effects of charging or
discharging the 50 pF capacitor. This means that the time, t8, quoted in the timing
characteristics, is the true bus relinquish time of the part, and is independent of
the bus loading.
7
ns min
SCLK falling edge to SDATA three-state.
200μA
I
OL
TO OUTPUT
PIN
1.4V
C
L
50pF
200μA
I
OH
Figure 2. Load Circuit for Digital Output Timing Specifications
Rev. C | Page 9 of 28
AD7466/AD7467/AD7468
Timing Example 2
TIMING EXAMPLES
The AD7466 can also operate with slower clock frequencies.
As shown in Figure 3, assuming VDD = 1.8 V, fSCLK = 2 MHz,
and a throughput of 50 kSPS gives a cycle time of tCONVERT + t8 +
Figure 3 shows some of the timing parameters from Table 4 in
the Timing Specifications section.
Timing Example 1
tQUIET = 20 μs. With tCONVERT = t2 + 15(1/fSCLK) = 55 ns + 7.5 μs =
As shown in Figure 3, fSCLK = 3.4 MHz and a throughput of
100 kSPS gives a cycle time of tCONVERT + t8 + tQUIET = 10 μs.
Assuming VDD = 1.8 V, tCONVERT = t2 + 15(1/fSCLK) = 55 ns +
4.41 μs = 4.46 μs, and t8 = 60 ns maximum, then tQUIET = 5.48 μs,
which satisfies the requirement of 10 ns for tQUIET. The part is
fully powered up and the signal is fully acquired at Point A.
This means that the acquisition/power-up time is t2 + 2(1/fSCLK
= 55 ns + 588 ns = 643 ns, satisfying the maximum requirement
of 640 ns for the power-up time.
7.55 μs, and t8 = 60 ns maximum, this leaves tQUIET to be 12.39
μs, which satisfies the requirement of 10 ns for tQUIET. The part is
fully powered up and the signal is fully acquired at Point A,
which means the acquisition/power-up time is t2 + 2(1/fSCLK) =
55 ns + 1 μs = 1.05 μs, satisfying the maximum requirement of
640 ns for the power-up time. In this example and with other
slower clock values, the part is fully powered up and the signal
already acquired before the third SCLK falling edge; however,
the track-and-hold does not go into hold mode until that point.
In this example, the part can be powered up and the signal can
be fully acquired at approximately Point B in Figure 3.
)
CS
tCONVERT
t2
B
A
SCLK
1
3
5
13
15
16
2
4
14
t8
tQUIET
ACQUISITION TIME
AUTOMATIC
POWER-DOWN
TRACK-AND-HOLD
IN TRACK
TRACK-AND-HOLD IN HOLD
1/THROUGHPUT
POINT A: THE PART IF FULLY POWERED UP WITH V FULLY ACQUIRED.
IN
Figure 3. AD7466 Serial Interface Timing Diagram Example
Rev. C | Page 10 of 28
AD7466/AD7467/AD7468
ABSOLUTE MAXIMUM RATINGS
TA = 25°C, unless otherwise noted. Transient currents of up to
100 mA do not cause SCR latch-up.
Stresses above those listed under Absolute Maximum Ratings
may cause permanent damage to the device. This is a stress
rating only; functional operation of the device at these or any
other conditions above those indicated in the operational
section of this specification is not implied. Exposure to absolute
maximum rating conditions for extended periods may affect
device reliability.
Table 5.
Parameter
Rating
VDD to GND
−0.3 V to +7 V
−0.3 V to VDD + 0.3 V
−0.3 V to +7 V
−0.3 V to VDD + 0.3 V
10 mA
Analog Input Voltage to GND
Digital Input Voltage to GND
Digital Output Voltage to GND
Input Current to any Pin Except Supplies
Operating Temperature Range
Commercial (B Version)
Storage Temperature Range
Junction Temperature
SOT-23 Package
ESD CAUTION
−40°C to +85°C
−65°C to +150°C
150°C
θJA Thermal Impedance
θJC Thermal Impedance
MSOP Package
229.6°C/W
91.99°C/W
θJA Thermal Impedance
θJC Thermal Impedance
Lead Temperature, Soldering
Vapor Phase (60 sec)
Infrared (15 sec)
205.9°C/W
43.74°C/W
215°C
220°C
3.5 kV
ESD
Rev. C | Page 11 of 28
AD7466/AD7467/AD7468
PIN CONFIGURATIONS AND FUNCTION DESCRIPTIONS
1
2
3
4
8
7
6
5
V
DD
1
2
3
6
5
4
CS
CS
V
DD
AD7466/
AD7467/
AD7468
ꢀ
ꢀ
AD7466/
AD7467/
AD7468
TOP VIEW
(Not to Scale)
SDATA
SCLK
GND
SDATA
SCLK
NC
GND
V
V
IN
IN
TOP VIEW
(Not to Scale)
NC
NC = NO CONNECT
Figure 4. SOT-23 Pin Configuration
Figure 5. MSOP Pin Configuration
Table 6. Pin Function Descriptions
Pin No.
Mnemonic Description
SOT-23 MSOP
6
1
CS
Chip Select. Active low logic input. This input provides the dual function of initiating conversions on the
devices and frames the serial data transfer.
1
2
8
7
VDD
GND
Power Supply Input. The VDD range for the devices is from 1.6 V to 3.6 V.
Analog Ground. Ground reference point for all circuitry on the devices. All analog input signals should
be referred to this GND voltage.
3
5
6
2
VIN
SDATA
Analog Input. Single-ended analog input channel. The input range is 0 V to VDD.
Data Out. Logic output. The conversion result from the AD7466/AD7467/AD7468 is provided on this
output as a serial data stream. The bits are clocked out on the falling edge of the SCLK input. The data
stream from the AD7466 consists of four leading zeros followed by the 12 bits of conversion data,
provided MSB first. The data stream from the AD7467 consists of four leading zeros followed by the 10
bits of conversion data, provided MSB first. The data stream from the AD7468 consists of four leading
zeros followed by the 8 bits of conversion data, provided MSB first.
4
3
SCLK
NC
Serial Clock. Logic input. SCLK provides the serial clock for accessing data from the parts. This clock
input is also used as the clock source for the conversion process of the parts.
No Connect.
4, 5
Rev. C | Page 12 of 28
AD7466/AD7467/AD7468
TYPICAL PERFORMANCE CHARACTERISTICS
SCLK frequency of 3.4 MHz, and sampling at a rate of 100 kSPS
for the AD7466 (see the Analog Input section).
DYNAMIC PERFORMANCE CURVES
Figure 6, Figure 7, and Figure 8 show typical FFT plots for the
AD7466, AD7467, and AD7468, respectively, at a 100 kSPS
sample rate and a 30 kHz input tone.
DC ACCURACY CURVES
Figure 13 and Figure 14 show typical INL and DNL perform-
ance for the AD7466.
Figure 9 shows the signal-to-noise and distortion ratio
performance vs. input frequency for various supply voltages
while sampling at 100 kSPS with an SCLK frequency of 3.4 MHz
for the AD7466.
POWER REQUIREMENT CURVES
Figure 15 shows the supply current vs. supply voltage for the
AD7466 at −40°C, +25°C, and +85°C, with SCLK frequency of
3.4 MHz and a sampling rate of 100 kSPS.
Figure 10 shows the signal-to-noise ratio (SNR) performance
vs. input frequency for various supply voltages while sampling
at 100 kSPS with an SCLK frequency of 3.4 MHz for the
AD7466.
Figure 16 shows the maximum current vs. supply voltage for the
AD7466 with different SCLK frequencies.
Figure 17 shows the shutdown current vs. supply voltage.
Figure 11 shows the total harmonic distortion (THD) vs. analog
input signal frequency for various supply voltages while sam-
pling at 100 kSPS with an SCLK frequency of 3.4 MHz for
the AD7466.
Figure 18 shows the power consumption vs. throughput rate for
the AD7466 with an SCLK of 3.4 MHz and different supply
voltages. See the Power Consumption section for more details.
Figure 12 shows the THD vs. analog input frequency for
different source impedances with a supply voltage of 2.7 V, an
15
25
8192 POINT FFT
8192 POINT FFT
V
f
= 1.8V
V
= 1.8V
= 100kSPS
= 30kHz
DD
DD
= 100kSPS
f
f
5
–15
–35
–55
–75
–95
–115
SAMPLE
SAMPLE
–5
–25
f
= 30kHz
IN
IN
SINAD = 61.51dB
THD = –80.61dB
SFDR = –82.10dB
SINAD = 70.82dB
THD = –84.18dB
SFDR = –85.48dB
–45
–65
–85
–105
0
5
10
15
20
25
30
35
40
45
50
0
5
10
15
20
25
30
35
40
45
50
FREQUENCY (kHz)
FREQUENCY (kHz)
Figure 7. AD7467 Dynamic Performance at 100 kSPS
Figure 6. AD7466 Dynamic Performance at 100 kSPS
Rev. C | Page 13 of 28
AD7466/AD7467/AD7468
–65
–67
–69
–71
–73
–75
–77
–79
–81
–83
–85
5
–5
8192 POINT FFT
TEMP = 25°C
V
f
= 1.8V
DD
= 100kSPS
SAMPLE
f
= 30kHz
IN
–15
–25
–35
–45
–55
–65
–75
–85
–95
SINAD = 49.83dB
THD = –79.37dB
SFDR = –70.46dB
V
= 1.8V
DD
V
= 2.2V
DD
V
= 1.6V
DD
V
= 3V
DD
V
= 3.6V
V
= 2.7V
DD
DD
0
5
10
15
20
25
30
35
40
45
50
10
100
INPUT FREQUENCY (kHz)
FREQUENCY (kHz)
Figure 11. AD7466 THD vs. Analog Input Frequency
at 100 kSPS for Various Supply Voltages
Figure 8. AD7468 Dynamic Performance at 100 kSPS
–76
–77
–78
–79
–80
–81
–82
–83
–84
–65
–66
–67
–68
–69
–70
–71
–72
–73
TEMP = 25°C
= 2.7V
TEMP = 25°C
V
DD
R
= 1kΩ
IN
R
= 10Ω
IN
V
= 1.8V
V
= 1.6V
V
= 2.2V
DD
DD
DD
R
= 510Ω
R
= 100Ω
IN
IN
V
= 3.6V
V
= 3V
V
= 2.7V
DD
DD
DD
R
= 0Ω
IN
10
100
10
100
INPUT FREQUENCY (kHz)
INPUT FREQUENCY (kHz)
Figure 9. AD7466 SINAD vs. Analog Input Frequency
at 100 kSPS for Various Supply Voltages
Figure 12. AD7466 THD vs. Analog Input Frequency
for Various Source Impedances
–68.0
–68.5
–69.0
–69.5
–70.0
–70.5
–71.0
–71.5
–72.0
–72.5
–73.0
1.0
0.8
V
= 1.8V
TEMP = 25°C
DD
TEMP = 25°C
fIN = 50Hz
fSAMPLE = 100kSPS
0.6
0.4
0.2
V
= 1.6V
DD
V
= 1.8V
DD
0
V
= 2.2V
DD
–0.2
–0.4
–0.6
–0.8
–1.0
V
= 3.6V
V
= 3V
V
= 2.7V
DD
DD
DD
0
512
1024 1536 2048 2560 3072 3584
CODE
4096
10
100
INPUT FREQUENCY (kHz)
Figure 13. AD7466 INL Performance
Figure 10. AD7466 SNR vs. Analog Input Frequency
at 100 kSPS for Various Supply Voltages
Rev. C | Page 14 of 28
AD7466/AD7467/AD7468
1.0
0.8
2.5
2.0
1.5
1.0
0.5
0
V
= 1.8V
DD
TEMP = 25°C
fIN = 50Hz
fSAMPLE = 100kSPS
0.6
TEMP = +85°C
0.4
0.2
0
–0.2
–0.4
–0.6
–0.8
TEMP = +25°C
TEMP = –40°C
0
512
1024 1536 2048 2560 3072 3584
CODE
4096
1.5
2.0
2.5
3.0
3.5
4.0
SUPPLY VOLTAGE (V)
Figure 17. Shutdown Current vs. Supply Voltage
Figure 14. AD7466 DNL Performance
1.4
1.2
1.0
0.8
0.6
0.4
0.2
0
290
265
240
215
190
165
140
115
90
fSAMPLE = 100kSPS
TEMP = –40°C
TEMP = 25°C
V
V
= 3.0V
DD
DD
TEMP = +25°C
= 2.7V
V
V
= 2.2V
= 1.8V
DD
DD
TEMP = +85°C
65
0
50
100
150
200
250
1.4 1.6 1.8 2.0 2.2 2.4 2.6 2.8 3.0 3.2 3.4 3.6 3.8
SUPPLY VOLTAGE (V)
THROUGHPUT (kSPS)
Figure 15. AD7466 Supply Current vs. Supply Voltage, SCLK 3.4 MHz
Figure 18. AD7466 Power Consumption vs. Throughput Rate, SCLK 3.4 MHz
560
TEMP = 25°C
500
fSCLK = 3.4MHz, fSAMPLE = 200kSPS
440
fSCLK = 2.4MHz, fSAMPLE = 140kSPS
380
320
260
200
fSCLK = 1.2MHz, fSAMPLE = 50kSPS
140
80
1.4 1.6 1.8 2.0 2.2 2.4 2.6 2.8 3.0 3.2 3.4 3.6 3.8
SUPPLY VOLTAGE (V)
Figure 16. AD7466 Maximum Current vs. Supply Voltage
for Different SCLK Frequencies
Rev. C | Page 15 of 28
AD7466/AD7467/AD7468
TERMINOLOGY
Integral Nonlinearity (INL)
Signal-to-Noise and Distortion Ratio (SINAD)
The measured ratio of signal-to-noise and distortion at the
output of the ADC. The signal is the rms value of the sine wave,
and noise is the rms sum of all nonfundamental signals up to
half the sampling frequency (fS/2), including harmonics, but
excluding dc.
The maximum deviation from a straight line passing through
the endpoints of the ADC transfer function. For the AD7466/
AD7467/AD7468, the endpoints of the transfer function are
zero scale, a point 1 LSB below the first code transition, and full
scale, a point 1 LSB above the last code transition.
Differential Nonlinearity (DNL)
Total Unadjusted Error (TUE)
The difference between the measured and the ideal 1 LSB
change between any two adjacent codes in the ADC.
A comprehensive specification that includes gain error, linearity
error, and offset error.
Offset Error
Total Harmonic Distortion (THD)
The deviation of the first code transition (00 . . . 000) to
(00 . . . 001) from the ideal (that is, AGND + 1 LSB).
The ratio of the rms sum of harmonics to the fundamental. For
the AD7466/AD7467/AD7468, it is defined as
Gain Error
V22 +V32 +V42 +V52 +V62
The deviation of the last code transition (111 . . . 110) to
(111…111) from the ideal (that is, VREF − 1 LSB) after the offset
error has been adjusted out.
(
)
THD dB = 20 log
V1
where V1 is the rms amplitude of the fundamental, and V2, V3,
V4, V5, and V6 are the rms amplitudes of the second through
sixth harmonics.
Track-and-Hold Acquisition Time
The time required for the part to acquire a full-scale step
input value within 1 LSB, or a 30 kHz ac input value within
0.5 LSB. The AD7466/AD7467/AD7468 enter track mode on
Peak Harmonic or Spurious Noise (SFDR)
The ratio of the rms value of the next-largest component in the
ADC output spectrum (up to fS/2 and excluding dc) to the rms
value of the fundamental. Typically, the value of this specifica-
tion is determined by the largest harmonic in the spectrum, but
for ADCs where the harmonics are buried in the noise floor, it
is a noise peak.
CS
the
falling edge. The parts remain in hold mode until the following
CS
falling edge, and return to hold mode on the third SCLK
falling edge. See Figure 3 and the Serial Interface section for
more details.
Signal-to-Noise Ratio (SNR)
Intermodulation Distortion (IMD)
The measured ratio of signal to noise at the output of the ADC.
The signal is the rms value of the sine wave input. Noise is the
rms quantization error within the Nyquist bandwidth (fS/2).
The rms value of the sine wave is half of its peak-to-peak value
divided by √2, and the rms value for the quantization noise is
q/√12. The ratio depends on the number of quantization levels
in the digitization process; the more levels, the smaller the
quantization noise.
With inputs consisting of sine waves at two frequencies, fa
and fb, any active device with nonlinearities creates distortion
products at sum and difference frequencies of mfa nfb, where
m, n = 0, 1, 2, 3, and so on. Intermodulation distortion terms
are those for which neither m nor n are equal to zero. For
example, the second-order terms include (fa + fb) and (fa − fb),
while the third-order terms include (2fa + fb), (2fa – fb),
(fa + 2fb), and (fa − 2fb).
For an ideal N-bit converter, the SNR is defined as
The AD7466/AD7467/AD7468 are tested using the CCIF
standard where two input frequencies are used. In this case,
the second-order terms are usually distanced in frequency from
the original sine waves, while the third-order terms are usually
at a frequency close to the input frequencies. As a result, the
second- and third-order terms are specified separately. The
calculation of the intermodulation distortion is as per the
THD specification, where it is the ratio of the rms sum of the
individual distortion products to the rms amplitude of the sum
of the fundamentals, expressed in dB.
SNR = 6.02 N + 1.76 db
Thus, for a 12-bit converter, it is 74 dB; for a 10-bit converter, it
is 62 dB; and for an 8-bit converter, it is 50 dB.
However, in practice, various error sources in the ADCs cause
the measured SNR to be less than the theoretical value. These
errors occur due to integral and differential nonlinearities,
internal ac noise sources, and so on.
Rev. C | Page 16 of 28
AD7466/AD7467/AD7468
THEORY OF OPERATION
CHARGE
REDISTRIBUTION
DAC
CIRCUIT INFORMATION
The AD7466/AD7467/AD7468 are fast, micropower, 12-bit,
10-bit, and 8-bit ADCs, respectively. The parts can be operated
from a 1.6 V to 3.6 V supply. When operated from any supply
voltage within this range, the AD7466/AD7467/AD7468 are
capable of throughput rates of 200 kSPS when provided with a
3.4 MHz clock.
SAMPLING
CAPACITOR
A
V
IN
CONTROL
LOGIC
SW1
SW2
CONVERSION
PHASE
B
COMPARATOR
AGND
V
/2
DD
Figure 20. ADC Conversion Phase
The AD7466/AD7467/AD7468 provide the user with an on-
chip track-and-hold, an ADC, and a serial interface housed in a
tiny 6-lead SOT-23 or an 8-lead MSOP package, which offer the
user considerable space-saving advantages over alternative
solutions. The serial clock input accesses data from the part, but
also provides the clock source for the successive approximation
ADC. The analog input range is 0 V to VDD. An external refer-
ence is not required for the ADC, and there is no on-chip
reference. The reference for the AD7466/AD7467/AD7468 is
derived from the power supply, thus giving the widest possible
dynamic input range.
ADC TRANSFER FUNCTION
The output coding of the AD7466/AD7467/AD7468 is straight
binary. The designed code transitions occur at successive
integer LSB values; that is, 1 LSB, 2 LSB, and so on. The LSB size
for the devices is as follows:
VDD/4096 for the AD7466
VDD/1024 for the AD7467
VDD/256 for the AD7468
The ideal transfer characteristics for the devices are shown in
Figure 21.
The AD7466/AD7467/AD7468 also feature an automatic
power-down mode to allow power savings between conversions.
The power-down feature is implemented across the standard
serial interface, as described in the Normal Mode section.
111...111
111...110
CONVERTER OPERATION
111...000
011...111
The AD7466/AD7467/AD7468 are successive approximation
analog-to-digital converters based around a charge redistribu-
tion DAC. Figure 19 and Figure 20 show simplified schematics
of the ADC. Figure 19 shows the ADCs during the acquisition
phase. SW2 is closed and SW1 is in Position A, the comparator
is held in a balanced condition, and the sampling capacitor
acquires the signal on VIN.
1LSB = V /4096 (AD7466)
DD
1LSB = V /1024 (AD7467)
DD
1LSB = V /256 (AD7468)
DD
000...010
000...001
000...000
0V 1LSB
+V – 1LSB
DD
ANALOG INPUT
Figure 21. AD7466/AD7467/AD7468 Transfer Characteristics
CHARGE
REDISTRIBUTION
DAC
TYPICAL CONNECTION DIAGRAM
SAMPLING
CAPACITOR
A
Figure 22 shows a typical connection diagram for the devices.
VREF is taken internally from VDD and, therefore, VDD should
be well decoupled. This provides an analog input range of
0 V to VDD.
V
IN
CONTROL
LOGIC
SW1
B
ACQUISITION
PHASE
SW2
COMPARATOR
AGND
V
/2
DD
2.5V
5V
SUPPLY
REF192
Figure 19. ADC Acquisition Phase
1μF
TANT
0.1μF
10μF
0.1μF
240μA
When the ADC starts a conversion, as shown in Figure 20,
SW2 opens and SW1 moves to Position B, causing the com-
parator to become unbalanced. The control logic and the
charge redistribution DAC are used to add and subtract fixed
amounts of charge from the sampling capacitor to bring the
comparator back into a balanced condition. When the com-
parator is rebalanced, the conversion is complete. The control
logic generates the ADC output code. Figure 21 shows the ADC
transfer function.
680nF
V
DD
0VTOV
DD
SCLK
V
IN
INPUT
μC/μP
AD7466
SDATA
CS
GND
SERIAL
INTERFACE
Figure 22. REF192 as Power Supply to AD7466
Rev. C | Page 17 of 28
AD7466/AD7467/AD7468
V
DD
The conversion result consists of four leading zeros followed by
the MSB of the 12-bit, 10-bit, or 8-bit result from the AD7466,
AD7467, or AD7468, respectively. See the Serial Interface
section. Alternatively, because the supply current required by
the AD7466/AD7467/AD7468 is so low, a precision reference
can be used as the supply source to the devices.
C2
20pF
D1
R1
V
IN
C1
4pF
D2 CONVERSION PHASE—SWITCH OPEN
TRACK PHASE—SWITCH CLOSED
The REF19x series devices are precision micropower, low drop-
out voltage references. For the AD7466/AD7467/AD7468
voltage range operation, the REF193, REF192, and REF191 can
be used to supply the required voltage to the ADC, delivering
3 V, 2.5 V, and 2.048 V, respectively (see Figure 22). This con-
figuration is especially useful if the power supply is quite noisy
or if the system supply voltages are at a value other than 3 V or
2.5 V (for example, 5 V). The REF19x outputs a steady voltage
to the AD7466/AD7467/AD7468. If the low dropout REF192 is
used when the AD7466 is converting at a rate of 100 kSPS, the
REF192 needs to supply a maximum of 240 μA to the AD7466.
The load regulation of the REF192 is typically 10 ppm/mA
(REF192, VS = 5 V), which results in an error of 2.4 ppm (6 μV)
for the 240 μA drawn from it. This corresponds to a 0.0098 LSB
error for the AD7466 with VDD = 2.5 V from the REF192. For
applications where power consumption is important, the
automatic power-down mode of the ADC and the sleep mode
of the REF19x reference should be used to improve power
performance. See the Normal Mode section.
Figure 23. Equivalent Analog Input Circuit
For ac applications, removing high frequency components
from the analog input signal by using a band-pass filter on
the relevant analog input pin is recommended. In applications
where harmonic distortion and signal-to-noise ratio are critical,
the analog input should be driven from a low impedance
source. Large source impedances significantly affect the ac
performance of the ADC. This might necessitate the use of an
input buffer amplifier. The choice of the op amp is a function of
the particular application.
Table 8 provides typical performance data for various op amps
used as the input buffer under constant setup conditions.
Table 8. AD7466 Performance for Input Buffers
Op Amp in the
Input Buffer
AD7466 SNR Performance (dB)
30 kHz Input, VDD = 1.8 V
AD8510
AD8610
AD797
70.75
71.45
71.42
Table 7 provides some typical performance data with various
references used as a VDD source under the same setup
conditions. The ADR318, for instance, is a 1.8 V band gap
voltage reference. Its tiny footprint, low power consumption,
and additional shutdown capability make the ADR318 ideal for
battery-powered applications.
When no amplifier is used to drive the analog input, the source
impedance should be limited to low values. The maximum
source impedance depends on the amount of total harmonic
distortion (THD) that can be tolerated. The THD increases as
the source impedance increases and performance degrades.
Figure 12 shows a graph of THD vs. analog input signal
frequency for different source impedances when using a supply
voltage of 2.7 V and sampling at a rate of 100 kSPS.
Table 7. AD7466 Performance for Voltage Reference IC
Reference Tied to VDD
ADR318 @ 1.8 V
ADR370 @ 2.048 V
ADR421 @ 2.5 V
ADR423 @ 3 V
AD7466 SNR Performance (dB)
70.73
70.72
71.13
71.44
DIGITAL INPUTS
The digital inputs applied to the AD7466/AD7467/AD7468
are not limited by the maximum ratings that limit the analog
inputs. Instead, the digital inputs applied can go to 7 V and are
not restricted by the VDD + 0.3 V limit as on the analog input.
For example, if the AD7466/AD7467/AD7468 are operated with
a VDD of 3 V, 5 V logic levels could be used on the digital inputs.
However, the data output on SDATA still has 3 V logic levels
ANALOG INPUT
An equivalent circuit of the AD7466/AD7467/AD7468 analog
input structure is shown in Figure 23. The two diodes, D1 and
D2, provide ESD protection for the analog inputs. Care must be
taken to ensure that the analog input signal never exceeds the
supply rails by more than 300 mV. This causes these diodes to
become forward-biased and to start conducting current into the
substrate. Capacitor C1 in Figure 23 is typically about 4 pF and
can primarily be attributed to pin capacitance. Resistor R1 is a
lumped component made up of the on resistance of a switch.
This resistor is typically about 200 Ω. Capacitor C2 is the ADC
sampling capacitor with a typical capacitance of 20 pF.
CS
when VDD = 3 V. Another advantage of SCLK and
restricted by the VDD + 0.3 V limit is that power supply
CS
not being
sequencing issues are avoided. If
or SCLK is applied before
VDD, there is no risk of latch-up as there would be on the analog
inputs if a signal greater than 0.3 V is applied prior to VDD.
Rev. C | Page 18 of 28
AD7466/AD7467/AD7468
The AD7468 automatically enters power-down mode on the
12th SCLK falling edge.
NORMAL MODE
The AD7466/AD7467/AD7468 automatically enter power-
down at the end of each conversion. This mode of operation is
designed to provide flexible power management options and to
optimize the power dissipation/throughput rate ratio for low
power application requirements. Figure 24 shows the general
CS
The AD7466 also enters power-down mode if
high any time before the 16th SCLK falling edge. The conver-
CS
is brought
sion that was initiated by the
SDATA goes back into three-state. This also applies for the
CS
falling edge terminates and
CS
operation of the AD7466/AD7467/AD7468. On the
falling
AD7467 and AD7468; if
is brought high before the conver-
edge, the part begins to power up and the track-and-hold,
which was in hold while the part was in power-down, goes into
track mode. The conversion is also initiated at this point. On
sion is complete (the 14th SCLK falling edge for the AD7467,
and the 12th SCLK falling edge for the AD7468), the part enters
power-down, the conversion terminates, and SDATA goes back
into three-state.
CS
the third SCLK falling edge after the
and-hold returns to hold mode.
falling edge, the track-
CS
Although
CS
can idle high or low between conversions,
For the AD7466, 16 serial clock cycles are required to complete
the conversion and access the complete conversion result. The
AD7466 automatically enters power-down mode on the 16th
SCLK falling edge.
bringing
high once the conversion is complete is recom-
mended to save power.
When supplies are first applied to the devices, a dummy conver-
sion should be performed to ensure that the parts are in power-
down mode, the track-and-hold is in hold mode, and SDATA is
in three-state.
For the AD7467, 14 serial clock cycles are required to complete
the conversion and access the complete conversion result. The
AD7467 automatically enters power-down mode on the 14th
SCLK falling edge.
Once a data transfer is complete (SDATA has returned to three-
state), another conversion can be initiated after the quiet time,
For the AD7468, 12 serial clock cycles are required to complete
the conversion and access the complete conversion result.
CS
tQUIET, has elapsed, by bringing
low again.
AD7468 ENTERS POWER-DOWN
AD7467 ENTERS POWER-DOWN
THE PART BEGINS
TO POWER UP
THE PART IS POWERED UP
AND V FULLY ACQUIRED
IN
AD7466 ENTERS POWER-DOWN
CS
1
2
3
12
14
16
SCLK
SDATA
VALID DATA
Figure 24. Normal Mode Operation
Rev. C | Page 19 of 28
AD7466/AD7467/AD7468
This reduced power consumption can be seen in Figure 25,
which shows the supply current vs. SCLK frequency for various
supply voltages at a throughput rate of 100 kSPS. For a fixed
throughput rate, the supply current (average current) drops as
the SCLK frequency increases because the part is in power-
down mode most of the time. It can also be seen that, for a
lower supply voltage, the supply current drops accordingly.
POWER CONSUMPTION
The AD7466/AD7467/AD7468 automatically enter power-
down mode at the end of each conversion or if
high before the conversion is finished.
CS
is brought
When the AD7466/AD7467/AD7468 are in power-down mode,
all the analog circuitry is powered down and the current con-
sumption is typically 8 nA.
390
fSAMPLE = 100kSPS
To achieve the lowest power dissipation, there are some
considerations the user should keep in mind.
TEMP = 25°C
360
330
300
270
240
210
180
150
120
90
V
V
= 3.6V
= 3.0V
DD
DD
The conversion time is determined by the serial clock
frequency; the faster the SCLK frequency, the shorter the
conversion time. This implies that as the frequency increases,
the part dissipates power for a shorter period of time when the
conversion is taking place, and it remains in power-down mode
for a longer percentage of the cycle time or throughput rate.
V
V
= 2.7V
= 1.8V
DD
V
= 2.2V
DD
DD
Figure 26 shows two AD7466s running with two different
SCLK frequencies, SCLK A and SCLK B, with SCLK A having
the higher SCLK frequency. For the same throughput rate, the
AD7466 using SCLK A has a shorter conversion time than the
AD7466 using SCLK B, and it remains in power-down mode
longer. The current consumption in power-down mode is very
low; thus, the average power consumption is greatly reduced.
V
= 1.6V
2.4
DD
60
2.2
2.6
2.8
3.0
3.2
3.4
3.6
SCLK FREQUENCY (MHz)
Figure 25. Supply Current vs. SCLK Frequency
for a Fixed Throughput Rate and Different Supply Voltages
1/THROUGHPUT
CONVERSION TIME B
CONVERSION TIME A
CS
1
1
16
SCLK A
SCLK B
16
Figure 26. Conversion Time Comparison for Different SCLK Frequencies and a Fixed Throughput Rate
1/THROUGHPUT B
1/THROUGHPUT A
POWER DOWN TIME A
CONVERSION TIME A
CS A
POWER DOWN TIME B
CONVERSION TIME B
CS B
1
16
SCLK
Figure 27. Conversion Time vs. Power-Down Time for a Fixed SCLK Frequency and Different Throughput Rates
Rev. C | Page 20 of 28
AD7466/AD7467/AD7468
Figure 18 shows power consumption vs. throughput rate for a
3.4 MHz SCLK frequency. In this case, the conversion time is
the same for all cases because the SCLK frequency is a fixed
parameter. Low throughput rates lead to lower current con-
sumptions, with a higher percentage of the time in power-down
mode. Figure 27 shows two AD7466s running with the same
SCLK frequency, but at different throughput rates. The A
throughput rate is higher than the B throughput rate. The
slower the throughput rate, the longer the period of time the
part is in power-down mode, and the average power consump-
tion drops accordingly.
The average power consumption includes the power dissipated
when the part is converting and the power dissipated when the
part is in power-down mode. The average power dissipated
during conversion is calculated as the percentage of the cycle
time spent when converting, multiplied by the maximum
current during conversion. The average power dissipated in
power-down mode is calculated as the percentage of cycle time
spent in power-down mode, multiplied by the current figure for
power-down mode. In order to obtain the value for the average
power, these terms must be multiplied by the voltage.
Considering the maximum current for each SCLK frequency
for VDD = 1.8 V,
Figure 28 shows the power vs. throughput rate for different
supply voltages and SCLK frequencies. For this plot, all the
elements regarding power consumption that were explained
previously (the influence of the SCLK frequency, the influence
of the throughput rate, and the influence of the supply voltage)
are taken into consideration.
Power Consumption A = ((4.7/20) × 186 μA + (15.3/20) ×
100 nA) × 1.8 V = (43.71 + 0.076) μA × 1.8 V = 78.8 μW
= 0.07 mW
Power Consumption B = ((13/20) × 108 μA + (7/20) ×
100 nA) × 1.8 V = (70.2 + 0.035) μA × 1.8 V = 126.42 μW
= 0.126 mW
1.4
TEMP = 25°C
1.2
It can be concluded that for a fixed throughput rate, the average
power consumption drops as the SCLK frequency increases.
V
= 3.0V, SCLK = 2.4MHz
DD
1.0
0.8
0.6
0.4
0.2
0
Power Consumption Example 2
This example shows that, for a fixed SCLK frequency, as the
throughput rate decreases, the average power consumption
drops. From Figure 27, for SCLK = 3.4 MHz, Throughput A =
100 kSPS (which gives a cycle time of 10 μs), and Throughput B
= 50 kSPS (which gives a cycle time of 20 μs), the following
values can be obtained:
V
= 3.0V, SCLK = 3.4MHz
DD
V
= 1.8V, SCLK = 2.4MHz
DD
V
= 1.8V, SCLK = 3.4MHz
DD
Conversion Time A = 16 × (1/SCLK) = 4.7 μs
0
50
100
150
200
250
(47% of the cycle time for a throughput of 100 kSPS)
THROUGHPUT (kSPS)
Figure 28. Power vs. Throughput Rate
for Different SCLK and Supply Voltages
Power-Down Time A = (1/Throughput A) − Conversion
Time A = 10 μs − 4.7 μs = 5.3 μs (53% of the cycle time)
The following examples show calculations for the information
in this section.
Conversion Time B = 16 × (1/SCLK) = 4.7 μs
(23.5% of the cycle time for a throughput of 50 kSPS)
Power Consumption Example 1
Power-Down Time B = (1/Throughput B) − Conversion
Time B = 20 μs − 4.7 μs = 15.3 μs (76.5% of the cycle time)
This example shows that, for a fixed throughput rate, as the
SCLK frequency increases, the average power consumption
drops. From Figure 26, for SCLK A = 3.4 MHz, SCLK B =
1.2 MHz, and a throughput rate of 50 kSPS, which gives a cycle
time of 20 μs, the following values can be obtained:
The average power consumption is calculated as explained in
Power Consumption Example 1, considering the maximum
current for a 3.4 MHz SCLK frequency for VDD = 1.8 V.
Power Consumption A = ((4.7/10) × 186 μA + (5.3/10) ×
100 nA) × 1.8 V= (87.42 + 0.053) μA × 1.8 V = 157.4 μW =
0.157 mW
Conversion Time A = 16 × (1/SCLK A) = 4.7 μs
(23.5% of the cycle time)
Power-Down Time A = (1/Throughput) − Conversion
Time A = 20 μs − 4.7 μs = 15.3 μs (76.5% of the cycle time)
Power Consumption B = ((4.7/20) × 186 μA + (15.3/20) ×
100 nA) × 1.8 V = (43.7 + 0.076) μA × 1.8 V = 78.79 μW =
0.078 mW
Conversion Time B = 16 × (1/SCLK B) = 13 μs
(65% of the cycle time)
It can be concluded that for a fixed SCLK frequency, the average
power consumption drops as the throughput rate decreases.
Power-Down Time B = (1/Throughput) − Conversion
Time B = 20 μs − 13 μs = 7 μs (35% of the cycle time)
Rev. C | Page 21 of 28
AD7466/AD7467/AD7468
SERIAL INTERFACE
Figure 29, Figure 30, and Figure 31 show the timing diagrams
for serial interfacing to the AD7466/AD7467/AD7468. The
serial clock provides the conversion clock and controls the
transfer of information from the ADC during a conversion.
CS
occurs before 12 SCLKs elapse,
down. If the rising edge of
the conversion terminates, the SDATA line goes back into three-
state, and the AD7468 enters power-down; otherwise SDATA
returns to three-state on the 12th SCLK falling edge, as shown
in Figure 31. Twelve serial clock cycles are required to perform
the conversion process and to access data from the AD7468.
CS
The part begins to power up on the
falling edge. The falling
puts the track-and-hold into track mode and takes
the bus out of three-state. The conversion is also initiated at this
CS
CS
edge of
CS
going low provides the first leading zero to be read in by the
microcontroller or DSP. The remaining data is then clocked out
by subsequent SCLK falling edges, beginning with the second
leading zero; thus, the first clock falling edge on the serial clock
has the first leading zero provided and also clocks out the
second leading zero. For the AD7466, the final bit in the data
transfer is valid on the 16th SCLK falling edge, having been
clocked out on the previous (15th) SCLK falling edge.
point. On the third SCLK falling edge after the
falling edge,
the part should be powered up fully at Point B, as shown in
Figure 29, and the track-and-hold returns to hold.
For the AD7466, the SDATA line goes back into three-state and
the part enters power-down on the 16th SCLK falling edge. If
CS
the rising edge of
occurs before 16 SCLKs elapse, the
conversion terminates, the SDATA line goes back into three-
state, and the part enters power-down; otherwise SDATA
returns to three-state on the 16th SCLK falling edge, as shown
in Figure 29. Sixteen serial clock cycles are required to perform
the conversion process and to access data from the AD7466.
In applications with a slow SCLK, it is possible to read in data
on each SCLK rising edge. In such a case, the first falling edge
CS
of SCLK after the
zero and can be read in the following rising edge. If the first
CS
falling edge clocks out the second leading
SCLK edge after the
falling edge is a falling edge, the first
CS
For the AD7467, the 14th SCLK falling edge causes the SDATA
line to go back into three-state, and the part enters power-down.
leading zero that was clocked out when
went low is missed,
unless it is not read on the first SCLK falling edge. The 15th
falling edge of SCLK clocks out the last bit, and it can be read in
the following rising SCLK edge.
CS
If the rising edge of
occurs before 14 SCLKs elapse, the con-
version terminates, the SDATA line goes back into three-state,
and the AD7467 enters power-down; otherwise SDATA returns
to three-state on the 14th SCLK falling edge, as shown in Figure 30.
Fourteen serial clock cycles are required to perform the
conversion process and to access data from the AD7467.
CS
CS
falling edge is a rising edge,
If the first SCLK edge after the
clocks out the first leading zero, and it can be read on the SCLK
rising edge. The next SCLK falling edge clocks out the second
leading zero, and it can be read on the following rising edge.
For the AD7468, the 12th SCLK falling edge causes the SDATA
line to go back into three-state, and the part enters power-
t1
CS
tCONVERT
t2
t6
B
SCLK
1
2
3
4
5
13
14
t5
15
16
t8
t3
t4
t7
tQUIET
SDATA
0
0
0
0
DB11
DB10
DB2
DB1
DB0
THREE-STATE
THREE-STATE
4 LEADING ZEROS
12 BITS OF DATA
Figure 29. AD7466 Serial Interface Timing Diagram
t1
CS
tCONVERT
t6
t2
B
1
2
3
4
5
13
t5
14
t8
SCLK
t7
t3
tQUIET
t4
DB9
DB8
10 BITS OF DATA
DB0
0
0
0
SDATA
0
THREE-STATE
THREE-STATE
4 LEADING ZEROS
Figure 30. AD7467 Serial Interface Timing Diagram
Rev. C | Page 22 of 28
AD7466/AD7467/AD7468
t1
CS
tCONVERT
t6
t2
B
1
2
3
4
11
12
SCLK
t8
t5
t7
tQUIET
t3
t4
0
0
0
0
DB7
DB0
8 BITS OF DATA
SDATA
THREE-STATE
THREE-STATE
4 LEADING ZEROS
Figure 31. AD7468 Serial Interface Timing Diagram
Figure 32 shows the connection diagram. For signal processing
applications, it is imperative that the frame synchronization
signal from the TMS320C541 provide equidistant sampling.
MICROPROCESSOR INTERFACING
The serial interface on the AD7466/AD7467/AD7468 allows
the parts to be connected directly to many different micro-
processors. This section explains how to interface the AD7466/
AD7467/AD7468 with some of the more common microcontroller
and DSP serial interface protocols.
AD7466/
AD7467/
AD74681
TMS320C5411
SCLK
CLKX
AD7466/AD7467/AD7468 to TMS320C541 Interface
CLKR
DR
SDATA
CS
The serial interface on the TMS320C541 uses a continuous
serial clock and frame synchronization signals to synchronize
the data transfer operations with peripheral devices like the
FSX
FSR
CS
AD7466/AD7467/AD7468. The
input allows easy inter-
1
ADDITIONAL PINS OMITTED FOR CLARITY.
facing between the TMS320C541 and the AD74xx devices,
without requiring any glue logic. The serial port of the
TMS320C541 is set up to operate in burst mode (FSM = 1
in the serial port control register, SPC) with internal CLKX
(MCM = 1 in the SPC register) and internal frame signal
(TXM = 1 in the SPC register), so both pins are configured as
outputs. For the AD7466, the word length should be set to
16 bits (FO = 0 in the SPC register). The standard synchronous
serial port interface in this DSP allows only frames with a word
length of 16 bits or 8 bits. Therefore, for the AD7467 and
AD7468 where 14 and 12 bits are required, the FO bit also
would be set up to 16 bits. In these cases, the user should keep
in mind that the last 2 bits and 4 bits for the AD7467 and
AD7468, respectively, are invalid data as the SDATA line goes
back into three-state on the 14th and 12th SCLK falling edge.
Figure 32. Interfacing to the TMS320C541
AD7466/AD7467/AD7468 to ADSP-218x Interface
The ADSP-218x family of DSPs is interfaced directly to the
AD7466/AD7467/AD7468 without any glue logic. The SPORT
control register must be set up as described in Table 9.
Table 9. SPORT Control Register Setup
Setting
Description
TFSW = RFSW = 1
INVRFS = INVTFS = 1
DTYPE = 00
ISCLK = 1
TFSR = RFSR = 1
IRFS = 0
Alternate framing
Active low frame signal
Right-justify data
Internal serial clock
Frame every word
Sets up RFS as an input
Sets up TFS as an output
16 bits for the AD7466
14 bits for the AD7467
12 bits for the AD7468
ITFS = 1
To summarize, the values in the SPC register are FO = 0,
FSM = 1, MCM = 1, and TXM = 1.
SLEN = 1111
SLEN = 1101
SLEN = 1011
Rev. C | Page 23 of 28
AD7466/AD7467/AD7468
The connection diagram in Figure 33 shows how the ADSP-218x
has the TFS and RFS of the SPORT tied together, with TFS set
as an output and RFS set as an input. The DSP operates in
alternate framing mode, and the SPORT control register is set
up as described. The frame synchronization signal generated on
AD7466/AD7467/AD7468 to DSP563xx Interface
The connection diagram in Figure 34 shows how the AD7466/
AD7467/AD7468 can be connected to the synchronous serial
interface (SSI) of the DSP563xx family of DSPs from Motorola.
The SSI is operated in synchronous mode and normal mode
(SYN = 1 and MOD = 0 in Control Register B, CRB) with an
internally generated word frame sync for both Tx and Rx
(Bit FSL1 = 0 and Bit FSL0 = 0 in the CRB register). Set the
word length in Control Register A (CRA) to 16 by setting Bits
WL2 = 0, WL1 = 1, and WL0 = 0 for the AD7466. The word
length for the AD7468 can be set to 12 bits (WL2 = 0, WL1 = 0,
and WL0 = 1). This DSP does not offer the option for a 14-bit
word length, so the AD7467 word length is set up to 16 bits like
the AD7466 word length. In this case, the user should keep in
mind that the last two bits are invalid data because the SDATA
goes back into three-state on the 14th SCLK falling edge.
CS
the TFS is tied to , and as with all signal processing applica-
tions, equidistant sampling is necessary. However, in this example,
the timer interrupt is used to control the sampling rate of the
ADC and, under certain conditions, equidistant sampling might
not be achieved.
The timer registers, for example, are loaded with a value that
provides an interrupt at the required sample interval. When an
interrupt is received, a value is transmitted with TFS/DT (ADC
control word). The TFS is used to control the RFS and, there-
fore, the reading of data. The frequency of the serial clock is set
in the SCLKDIV register. When the instruction to transmit with
TFS is given (that is, AX0 = TX0), the state of the SCLK is
checked. The DSP waits until the SCLK goes high, low, and high
again before transmission starts. If the timer and SCLK values
are chosen such that the instruction to transmit occurs on or
near the rising edge of SCLK, the data can be transmitted, or it
can wait until the next clock edge.
The frame sync polarity bit (FSP) in the CRB register can be set
to 1, which means the frame goes low and a conversion starts.
Likewise, by means of Bits SCD2, SCKD, and SHFD in the CRB
register, it is established that Pin SC2 (the frame sync signal)
and Pin SCK in the serial port are configured as outputs, and
the most significant bit (MSB) is shifted first. To summarize,
For example, the ADSP-2181 has a master clock frequency of
16 MHz. If the SCLKDIV register is loaded with the value 3, an
SCLK of 2 MHz is obtained, and eight master clock periods
elapse for every SCLK period. If the timer registers are loaded
with the value 803, 100.5 SCLKs occur between interrupts and,
subsequently, between transmit instructions. This situation
results in nonequidistant sampling as the transmit instruction is
occurring on an SCLK edge. If the number of SCLKs between
interrupts is a whole integer figure of N, equidistant sampling is
implemented by the DSP.
MOD = 0
SYN = 1
WL2, WL1, WL0 depend on the word length
FSL1 = 0, FSL0 = 0
FSP = 1, negative frame sync
SCD2 = 1
SCKD = 1
SHFD = 0
For signal processing applications, it is imperative that the
frame synchronization signal from the DSP563xx provides
equidistant sampling.
AD7466/
AD7467/
AD74681
ADSP-218x1
AD7466/
AD7467/
AD74681
DSP563xx1
SCLK
SCLK
DR
SDATA
CS
SCLK
SCK
SRD
SC2
RFS
TFS
SDATA
CS
1
ADDITIONAL PINS OMITTED FOR CLARITY.
Figure 33. Interfacing to the ADSP-218x
1
ADDITIONAL PINS OMITTED FOR CLARITY.
Figure 34. Interfacing to the DSP563xx
Rev. C | Page 24 of 28
AD7466/AD7467/AD7468
APPLICATION HINTS
component side of the board is dedicated to ground planes,
while signals are placed on the solder side.
GROUNDING AND LAYOUT
The printed circuit board that houses the AD7466/AD7467/
AD7468 should be designed such that the analog and digital
sections are separated and confined to certain areas. This facili-
tates the use of ground planes that can be separated easily. A
minimum etch technique is generally best for ground planes
because it gives the best shielding. Digital and analog ground
planes should be joined at only one place. If the devices are in a
system where multiple devices require an AGND to DGND
connection, the connection should still be made at one point
only, a star ground point, which should be established as close
as possible to the AD7466/AD7467/AD7468.
Good decoupling is also very important. All analog supplies
should be decoupled with 10 μF tantalum in parallel with 0.1 μF
capacitors to AGND. All digital supplies should have a 0.1 μF
ceramic disc capacitor to DGND. To achieve the best perform-
ance from these decoupling components, the user should keep
the distance between the decoupling capacitor and the VDD and
GND pins to a minimum, with short track lengths connecting
the respective pins.
EVALUATING THE PERFORMANCE
OF THE AD7466 AND AD7467
Avoid running digital lines under the device because these
couple noise onto the die. The analog ground plane should be
allowed to run under the AD7466/AD7467/AD7468 to avoid
noise coupling. The power supply lines to the devices should
use as large a trace as possible to provide low impedance paths
and to reduce the effects of glitches on the power-supply line.
Fast switching signals, like clocks, should be shielded with
digital ground to avoid radiating noise to other sections of the
board, and clock signals should never be run near the analog
inputs. Avoid crossover of digital and analog signals. Traces on
opposite sides of the board should run at right angles to each
other to reduce the effects of feedthrough on the board. A
microstrip technique is the best choice, but is not always
possible with a double-sided board. With this technique, the
The evaluation board package includes a fully assembled and
tested evaluation board, documentation, and software for
controlling the board from the PC via an evaluation board
controller. To evaluate the ac and dc performance of the
AD7466 and AD7467, the evaluation board controller can be
used in conjunction with the AD7466/AD7467CB evaluation
board and other Analog Devices evaluation boards ending in
the CB designator.
The software allows the user to perform ac tests (fast Fourier
transform) and dc tests (histogram of codes) on the AD7466
and AD7467. See the data sheet in the evaluation board package
for more information.
Rev. C | Page 25 of 28
AD7466/AD7467/AD7468
OUTLINE DIMENSIONS
2.90 BSC
6
1
5
2
4
3
2.80 BSC
1.60 BSC
PIN 1
INDICATOR
0.95 BSC
1.90
BSC
1.30
1.15
0.90
1.45 MAX
0.22
0.08
10°
4°
0°
0.60
0.45
0.30
0.50
0.30
0.15 MAX
SEATING
PLANE
COMPLIANT TO JEDEC STANDARDS MO-178-AB
Figure 35. 6-Lead Small Outline Transistor Package [SOT-23]
(RJ-6)
Dimensions shown in millimeters
3.20
3.00
2.80
8
1
5
4
5.15
4.90
4.65
3.20
3.00
2.80
PIN 1
0.65 BSC
0.95
0.85
0.75
1.10 MAX
0.80
0.60
0.40
8°
0°
0.15
0.00
0.38
0.22
0.23
0.08
SEATING
PLANE
COPLANARITY
0.10
COMPLIANT TO JEDEC STANDARDS MO-187-AA
Figure 36. 8-Lead Mini Small Outline Package [MSOP]
(RM-8)
Dimensions shown in millimeters
Rev. C | Page 26 of 28
AD7466/AD7467/AD7468
ORDERING GUIDE
Model
AD7466BRT-REEL7
AD7466BRT-R2
AD7466BRTZ-REEL2
AD7466BRTZ-REEL72
AD7466BRTZ-R22
AD7466BRM
AD7466BRM-REEL
AD7466BRM-REEL7
AD7466BRMZ2
AD7466BRMZ-REEL2
AD7466BRMZ-REEL72
AD7467BRT-REEL
AD7467BRT-REEL7
AD7467BRT-R2
AD7467BRTZ-REEL2
AD7467BRTZ-REEL72
AD7467BRTZ-R22
AD7467BRM
Temperature Range
−40°C to +85°C
−40°C to +85°C
−40°C to +85°C
−40°C to +85°C
−40°C to +85°C
−40°C to +85°C
−40°C to +85°C
−40°C to +85°C
−40°C to +85°C
−40°C to +85°C
−40°C to +85°C
−40°C to +85°C
−40°C to +85°C
−40°C to +85°C
−40°C to +85°C
−40°C to +85°C
−40°C to +85°C
−40°C to +85°C
−40°C to +85°C
−40°C to +85°C
−40°C to +85°C
−40°C to +85°C
−40°C to +85°C
−40°C to +85°C
−40°C to +85°C
−40°C to +85°C
−40°C to +85°C
−40°C to +85°C
−40°C to +85°C
−40°C to +85°C
−40°C to +85°C
−40°C to +85°C
Linearity Error (LSB)1
1.5 max
1.5 max
1.5 max
1.5 max
1.5 max
1.5 max
1.5 max
1.5 max
1.5 max
1.5 max
1.5 max
0.5 max
0.5 max
0.5 max
0.5 max
0.5 max
0.5 max
0.5 max
0.5 max
0.5 max
0.5 max
0.2 max
0.2 max
0.2 max
0.2 max
0.2 max
0.2 max
0.2 max
0.2 max
0.2 max
0.2 max
0.2 max
Package Description
6-Lead SOT-23
6-Lead SOT-23
6-Lead SOT-23
6-Lead SOT-23
6-Lead SOT-23
8-Lead MSOP
8-Lead MSOP
8-Lead MSOP
8-Lead MSOP
8-Lead MSOP
8-Lead MSOP
6-Lead SOT-23
6-Lead SOT-23
6-Lead SOT-23
6-Lead SOT-23
6-Lead SOT-23
6-Lead SOT-23
8-Lead MSOP
8-Lead MSOP
8-Lead MSOP
8-Lead MSOP
6-Lead SOT-23
6-Lead SOT-23
6-Lead SOT-23
6-Lead SOT-23
6-Lead SOT-23
8-Lead MSOP
8-Lead MSOP
8-Lead MSOP
8-Lead MSOP
8-Lead MSOP
8-Lead MSOP
Evaluation Board
Evaluation Board
Control Board
Package Option
RJ-6
RJ-6
RJ-6
RJ-6
Branding
CLB
CLB
C2T
C2T
C2T
CLB
CLB
CLB
CLB#
CLB#
CLB#
CMB
CMB
CMB
CMB#
CMB#
CMB#
CMB
CMB
CMB
CMU
CNB
CNB
CNB
CNU#
CNU#
CNB
CNB
CNB
CNU#
CNU#
CNU#
RJ-6
RM-8
RM-8
RM-8
RM-8
RM-8
RM-8
RJ-6
RJ-6
RJ-6
RJ-6
RJ-6
RJ-6
RM-8
RM-8
RM-8
RM-8
RJ-6
RJ-6
RJ-6
RJ-6
RJ-6
RM-8
RM-8
RM-8
RM-8
RM-8
RM-8
AD7467BRM-REEL
AD7467BRM-REEL7
AD7467BRMZ2
AD7468BRT-REEL
AD7468BRT-REEL7
AD7468BRT-R2
AD7468BRTZ-REEL2
AD7468BRTZ-REEL72
AD7468BRM
AD7468BRM-REEL
AD7468BRM-REEL7
AD7468BRMZ2
AD7468BRMZ-REEL2
AD7468BRMZ-REEL72
EVAL-AD7466CB3
EVAL-AD7467CB3
EVAL-CONTROL BRD24
1 Linearity error refers to integral nonlinearity.
2 Z = RoHS Compliant Part, # denotes lead-free product may be top or bottom marked.
3 This can be used as a standalone evaluation board or in conjunction with the EVAL-CONTROL BRD2 for evaluation/demonstration purposes.
4 This board is a complete unit that allows a PC to control and communicate with all Analog Devices evaluation boards ending in the CB designator. For a complete
evaluation kit, order a particular ADC evaluation board (such as EVAL-AD7466CB), the EVAL-CONTROL BRD2, and a 12 V ac transformer. See relevant evaluation board
data sheets for more information.
Rev. C | Page 27 of 28
AD7466/AD7467/AD7468
NOTES
©2003–2007 Analog Devices, Inc. All rights reserved. Trademarks and
registered trademarks are the property of their respective owners.
C02643-0-5/07(C)
Rev. C | Page 28 of 28
AD7468BRMZ-REEL7 CAD模型
引脚图
封装焊盘图
AD7468BRMZ-REEL7 替代型号
| 型号 | 制造商 | 描述 | 替代类型 | 文档 |
| AD7468BRMZ | ADI | 1.6 V, Micropower 12-/10-/8-Bit ADCs | 完全替代 |
|
AD7468BRMZ-REEL7 相关器件
| 型号 | 制造商 | 描述 | 价格 | 文档 |
| AD7468BRT | ADI | 1.8 V, Micro-Power, 8/10/12-Bit ADCs in 6 Lead SOT-23 | 获取价格 |
|
| AD7468BRT-R | ADI | 1.6 V, Micropower 12-/10-/8-Bit ADCs | 获取价格 |
|
| AD7468BRT-REEL | ADI | 1.6 V, Micropower 12-/10-/8-Bit ADCs | 获取价格 |
|
| AD7468BRT-REEL7 | ADI | 1.6 V, Micropower 12-/10-/8-Bit ADCs | 获取价格 |
|
| AD7468BRT-RL2 | ADI | IC 1-CH 8-BIT SUCCESSIVE APPROXIMATION ADC, SERIAL ACCESS, PDSO6, MO-178AB, SOT-23, 6 PIN, Analog to Digital Converter | 获取价格 |
|
| AD7468BRTZ-REEL | ADI | 1.6 V, Micropower 12-/10-/8-Bit ADCs | 获取价格 |
|
| AD7468BRTZ-REEL7 | ADI | 1.6 V, Micropower 12-/10-/8-Bit ADCs | 获取价格 |
|
| AD7468_15 | ADI | 1.6 V, Micropower 12-/10-/8-Bit ADCs | 获取价格 |
|
| AD746A | ADI | Dual Precision, 500 ns Settling, BiFET Op Amp | 获取价格 |
|
| AD746AH | ETC | Voltage-Feedback Operational Amplifier | 获取价格 |
|
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