AD7575TQ [ADI]
LC2MOS 5 us 8-Bit ADC with Track/Hold; 5 LC2MOS我们8位ADC，带有采样/保持
| 型号： | AD7575TQ |
| 厂家： | 
ADI |
| 描述： | LC2MOS 5 us 8-Bit ADC with Track/Hold |
| 文件： | 总12页 (文件大小：149K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
LC2MOS
a
5 s 8-Bit ADC with Track/Hold
AD7575
FEATURES
FUNCTIONAL BLOCK DIAGRAM
Fast Conversion Time: 5 s
On-Chip Track/Hold
V
DD
Low Total Unadjusted Error: 1 LSB
Full Power Signal Bandwidth: 50 kHz
Single +5 V Supply
TRACK
AND
HOLD
AD7575
AIN
COMP
100 ns Data Access Time
Low Power (15 mW typ)
Low Cost
AGND
DAC
SAR
V
REF
Standard 18-Lead DlPs or 20-Terminal
Surface Mount Packages
CLOCK
OSCILLATOR
CLK
DB7
DB0
CS
RD
TP
LATCH AND
THREE STATE
OUTPUT DRIVERS
CONTROL
LOGIC
GENERAL DESCRIPTION
BUSY
DGND
The AD7575 is a high speed 8-bit ADC with a built-in track/
hold function. The successive approximation conversion tech-
nique is used to achieve a fast conversion time of 5 µs, while the
built-in track/hold allows full-scale signals up to 50 kHz (386 mV/µs
slew rate) to be digitized. The AD7575 requires only a single +5 V
supply and a low cost, 1.23 V bandgap reference in order to convert
PRODUCT HIGHLIGHTS
1. Fast Conversion Time/Low Power
The fast, 5 µs, conversion time of the AD7575 makes it
suitable for digitizing wideband signals at audio and ultra-
sonic frequencies while retaining the advantage of low
CMOS power consumption.
an input signal range of 0 to 2 VREF
.
The AD7575 is designed for easy interfacing to all popular 8-bit
microprocessors using standard microprocessor control signals
(CS and RD) to control starting of the conversion and reading of
the data. The interface logic allows the AD7575 to be easily
configured as a memory mapped device, and the part can be
interfaced as SLOW-MEMORY or ROM. All data outputs of
the AD7575 are latched and three-state buffered to allow direct
connection to a microprocessor data bus or I/O port.
2. On-Chip Track/Hold
The on-chip track/hold function is completely self-contained
and requires no external hold capacitor. Signals with slew
rates up to 386 mV/µs (e.g., 2.46 V peak-to-peak 50 kHz sine
waves) can be digitized with full accuracy.
3. Low Total Unadjusted Error
The zero, full-scale and linearity errors of the AD7575 are so
low that the total unadjusted error at any point on the trans-
fer function is less than 1 LSB, and offset and gain adjust-
ments are not required.
The AD7575 is fabricated in an advanced, all ion-implanted high
speed Linear Compatible CMOS (LC2MOS) process and is
available in a small, 0.3" wide, 18-lead DIP, 18-lead SOIC or in
other 20-terminal surface mount packages.
4. Single Supply Operation
Operation from a single +5 V supply with a low cost +1.23 V
bandgap reference allows the AD7575 to be used in 5 V
microprocessor systems without any additional power
supplies.
5. Fast Digital Interface
Fast interface timing allows the AD7575 to interface easily to
the fast versions of most popular microprocessors such as the
Z80H, 8085A-2, 6502B, 68B09 and the DSP processor, the
TMS32010.
REV. B
Information furnished by Analog Devices is believed to be accurate and
reliable. However, no responsibility is assumed by Analog Devices for its
use, nor for any infringements of patents or other rights of third parties
which may result from its use. No license is granted by implication or
otherwise under any patent or patent rights of Analog Devices.
One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A.
Tel: 781/329-4700
Fax: 781/326-8703
World Wide Web Site: http://www.analog.com
© Analog Devices, Inc., 1998
(VDD = +5 V, VREF = +1.23 V, AGND = DGND = 0 V; fCLK = 4 MHz external;
AD7575–SPECIFICATIONS all specifications TMIN to TMAX unless otherwise noted)
Parameter
J, A Versions1 K, B Versions S Version T Version
Units
Conditions/Comments
ACCURACY
Resolution
8
8
8
8
Bits
Total Unadjusted Error
Relative Accuracy
Minimum Resolution for Which
No Missing Codes Is Guaranteed
Full-Scale Error
±2
±1
±1
±1/2
±2
±1
±1
±1/2
LSB max
LSB max
8
8
8
8
Bits max
+25°C
±1
±1
±1
±1
±1
±1
±1
±1
LSB max Full-Scale TC Is Typically 5 ppm/°C
LSB max
T
MIN to TMAX
Offset Error2
+25°C
±1/2
±1/2
±1/2
±1/2
±1/2
±1/2
±1/2
±1/2
LSB max Offset TC Is Typically 5 ppm/°C
LSB max
TMIN to TMAX
ANALOG INPUT
Voltage Range
DC Input Impedance
Slew Rate, Tracking
SNR3
0 to 2 VREF
10
0.386
45
0 to 2 VREF
10
0.386
45
0 to 2 VREF 0 to 2 VREF
Volts
1 LSB = 2 VREF/256; See Figure 16
10
10
MΩ min
V/µs max
dB min
0.386
45
0.386
45
VIN = 2.46 V p-p @ 10 kHz; See Figure 11
REFERENCE INPUT
V
IREF
REF (For Specified Performance)
1.23
500
1.23
500
1.23
500
1.23
500
Volts
µA max
±5%
LOGIC INPUTS
CS, RD
VINL, Input Low Voltage
0.8
2.4
0.8
2.4
0.8
2.4
0.8
2.4
V max
V min
VINH, Input High Voltage
IIN, Input Current
+25°C
±1
±10
10
±1
±10
10
±1
±10
10
±1
±10
10
µA max
µA max
pF max
VIN = 0 or VDD
VIN = 0 or VDD
TMIN to TMAX
CIN, Input Capacitance3
CLK
VlNL, Input Low Voltage
VINH, Input High Voltage
IINL, Input Low Current
IINH, Input High Current
0.8
2.4
700
700
0.8
2.4
700
700
0.8
2.4
800
800
0.8
2.4
800
800
V max
V min
µA max
µA max
VINL = 0 V
VINH = VDD
LOGIC OUTPUTS
BUSY, DB0 to DB7
VOL, Output Low Voltage
VOH, Output High Voltage
DB0 to DB7
0.4
4.0
0.4
4.0
0.4
4.0
0.4
4.0
V max
V min
ISINK = 1.6 mA
ISOURCE = 40 µA
Floating State Leakage Current
±1
±1
10
±10
10
±10
10
µA max
pF max
VOUT = 0 to VDD
Floating State Output Capacitance3 10
CONVERSION TIME4
With External Clock
5
5
5
5
µs
fCLK = 4 MHz
With Internal Clock, TA = +25°C
5
15
5
15
5
15
5
15
µs min
µs max
Using Recommended Clock
Components Shown in Figure 15
POWER REQUIREMENTS5
VDD
IDD
+5
6
15
+5
6
15
+5
7
15
+5
7
15
Volts
mA max
mW typ
±5% for Specified Performance
Typically 3 mA with VDD = +5 V
Power Dissipation
Power Supply Rejection
±1/4
±1/4
±1/4
±1/4
LSB max 4.75 V ≤ VDD ≤ 5.25 V
NOTES
1Temperature ranges are as follows:
J, K Versions; 0°C to +70°C
A, B Versions; –25°C to +85°C
S, T Versions; –55°C to +125°C
2Offset error is measured with respect to an ideal first code transition that occurs at 1/2 LSB.
3Sample tested at +25°C to ensure compliance.
4Accuracy may degrade at conversion times other than those specified.
5Power supply current is measured when AD7575 is inactive i.e., when CS = RD = BUSY = logic HIGH.
Specifications subject to change without notice.
–2–
REV. B
AD7575
TIMING SPECIFICATIONS1 (VDD = +5 V, VREF = +1.23 V, AGND = DGND = 0 V)
Limit at +25؇C
(All Versions)
Limit at TMIN, TMAX
(J, K, A, B Versions)
Limit at TMIN, TMAX
(S, T Versions)
Parameter
Units
Conditions/Comments
t1
0
0
0
ns min
ns max
ns max
ns min
ns min
ns max
ns min
ns max
ns min
CS to RD Setup Time
RD to BUSY Propagation Delay
Data Access Time after RD
RD Pulse Width
CS to RD Hold Time
Data Access Time after BUSY
t22
100
100
100
0
80
10
80
0
100
100
100
0
80
10
80
0
120
120
120
0
100
10
t3
t4
t52
t63
t7
Data Hold Time
100
0
t8
BUSY to CS Delay
NOTES
1Timing specifications are sample tested at +25°C to ensure compliance. All input control signals are specified with tr = tf = 20 ns (10% to 90% of +5 V)
and timed from a voltage level of 1.6 V.
2t3 and t6 are measured with the load circuits of Figure 1 and defined as the time required for an output to cross 0.8 V or 2.4 V.
3t7 is defined as the time required for the data lines to change 0.5 V when loaded with the circuits of Figure 2.
Specifications subject to change without notice.
Test Circuits
+5V
3k⍀
+5V
3k⍀
DBN
DBN
DBN
DBN
3k⍀
10pF
3k⍀
100pF
10pF
100pF
DGND
DGND
DGND
DGND
a. VOH to High-Z
b. VOL to High-Z
a. High-Z to VOH
b High-Z to VOL
Figure 1. Load Circuits for Data Access Time Test
Figure 2. Load Circuits for Data Hold Time Test
ABSOLUTE MAXIMUM RATINGS*
VDD to AGND . . . . . . . . . . . . . . . . . . . . . . . . . . . –0.3 V, +7 V
Storage Temperature Range . . . . . . . . . . . . –65°C to +150°C
Lead Temperature (Soldering, 10 sec) . . . . . . . . . . . .+300°C
Power Dissipation (Any Package) to +75°C . . . . . . . 450 mW
Derates above +75°C by . . . . . . . . . . . . . . . . . . . . . 6 mW/°C
VDD to DGND . . . . . . . . . . . . . . . . . . . . . . . . . . . –0.3 V, +7 V
AGND to DGND . . . . . . . . . . . . . . . . . . . . . . . . –0.3 V, VDD
Digital Input Voltage to DGND . . . . . . . –0.3 V, VDD + 0.3 V
Digital Output Voltage to DGND . . . . . . –0.3 V, VDD + 0.3 V
CLK Input Voltage to DGND . . . . . . . . . –0.3 V, VDD + 0.3 V
VREF to AGND . . . . . . . . . . . . . . . . . . . . . . . . . . –0.3 V, VDD
AIN to AGND . . . . . . . . . . . . . . . . . . . . . . . . . . . –0.3 V, VDD
Operating Temperature Range
*Stresses above those listed under Absolute Maximum Ratings may cause perma-
nent damage to the device. This is a stress rating only; functional operation of the
device at these or any other conditions above those indicated in the operational
sections of this specification is not implied. Exposure to absolute maximum rating
conditions for extended periods may affect device reliability.
Commercial (J, K Versions) . . . . . . . . . . . . . . 0°C to +70°C
Industrial (A, B Versions) . . . . . . . . . . . . . –25°C to +85°C
Extended (S, T Versions) . . . . . . . . . . . . . –55°C to +125°C
CAUTION
ESD (electrostatic discharge) sensitive device. Electrostatic charges as high as 4000 V readily
accumulate on the human body and test equipment and can discharge without detection.
Although the AD7575 features proprietary ESD protection circuitry, permanent damage may
occur on devices subjected to high energy electrostatic discharges. Therefore, proper ESD
precautions are recommended to avoid performance degradation or loss of functionality.
WARNING!
ESD SENSITIVE DEVICE
REV. B
–3–
AD7575
PIN CONFIGURATIONS
LCCC
DIP/SOIC
PLCC
1
2
3
4
5
6
7
8
9
18
17
16
15
14
13
12
11
10
V
V
CS
RD
TP
DD
2
3
1
20 19
3
2
1
20 19
REF
PIN 1
IDENTIFIER
AIN
4
5
6
7
8
18
17
16
15
14
18
4
5
6
7
8
AIN
TP
AIN
BUSY
AGND
DB0 (LSB)
DB1
CLK
17
16
15
AGND
DB0 (LSB)
DB1
AGND
DB0 (LSB)
DB1
BUSY
CLK
BUSY
CLK
AD7575
TOP VIEW
(Not to Scale)
AD7575
TOP VIEW
(Not to Scale)
AD7575
TOP VIEW
(Not to Scale)
DB7 (MSB)
DB6
DB7 (MSB)
DB6
DB7 (MSB)
DB6
14 DB2
DB5
DB2
DB2
9
10 11 12 13
DB5
DB3
9
10 11 12 13
DGND
DB4
NC = NO CONNECT
NC = NO CONNECT
ORDERING GUIDE
Relative
TERMINOLOGY
LEAST SIGNIFICANT BIT (LSB)
An ADC with 8-bits resolution can resolve 1 part in 28 (i.e.,
256) of full scale. For the AD7575 with +2.46 V full-scale one
LSB is 9.61 mV.
Temperature
Range
Accuracy
(LSB)
Package
Options2
Model1
AD7575JR
AD7575JN
AD7575KN
AD7575JP
AD7575KP
AD7575AQ
AD7575BQ
AD7575SQ
AD7575TQ
AD7575SE
AD7575TE
0°C to +70°C
0°C to +70°C
0°C to +70°C
0°C to +70°C
±1 max
±1 max
±1/2 max
±1 max
±1/2 max
±1 max
±1/2 max
±1 max
±1/2 max
±1 max
R-18
TOTAL UNADJUSTED ERROR
This is a comprehensive specification that includes full-scale
error, relative accuracy and offset error.
N-18
N-18
P-20A
P-20A
Q-18
Q-18
Q-18
Q-18
E-20A
E-20A
0°C to +70°C
RELATIVE ACCURACY
–25°C to +85°C
–25°C to +85°C
–55°C to +125°C
–55°C to +125°C
–55°C to +125°C
–55°C to +125°C
Relative Accuracy is the deviation of the ADC’s actual code
transition points from a straight line drawn between the devices
measured first LSB transition point and the measured full-scale
transition point.
±1/2 max
SNR
Signal-to-Noise Ratio (SNR) is the ratio of the desired signal to
the noise produced in the sampled and digitized analog signal.
SNR is dependent on the number of quantization levels used in
the digitization process; the more levels, the smaller the quantiza-
tion noise. The theoretical SNR for a sine wave input is given by
NOTES
1To order MIL-STD-883, Class B process parts, add /883B to part number.
Contact local sales office for military data sheet. For U.S. Standard Military
Drawing (SMD), see DESC drawing #5962-87762.
2E = Leadless Ceramic Chip Carrier; N = Plastic DIP; P = Plastic Leaded Chip
Carrier; Q = Cerdip, R = SOIC.
SNR = (6.02 N + 1.76) dB
where N is the number of bits in the ADC.
FULL-SCALE ERROR (GAIN ERROR)
The gain of a unipolar ADC is defined as the difference between
the analog input levels required to produce the first and the last
digital output code transitions. Gain error is a measure of the
deviation of the actual span from the ideal span of FS – 2 LSBs.
ANALOG INPUT RANGE
With VREF = +1.23 V, the maximum analog input voltage range
is 0 V to +2.46 V. The output data in LSBs is related to the
analog input voltage by the integer value of the following
expression:
256 AIN
2 VREF
Data (LSBs) =
+ 0.5
SLEW RATE
Slew Rate is the maximum allowable rate of change of input
signal such that the digital sample values are not in error. Slew
Rate limitations may restrict the analog signal bandwidth for
full-scale analog signals below the bandwidth allowed from
sampling theorem considerations.
REV. B
–4–
AD7575
CS
RD
t1
t5
t2
tCONV
BUSY
t6
t7
t3
HIGH IMPEDANCE
BUS
NEW
DATA
HIGH IMPEDANCE
BUS
DATA
OLD DATA
Figure 3. Slow Memory Interface Timing Diagram
The major advantage of this interface is that it allows the micro-
processor to start conversion, WAIT, and then READ data with
a single READ instruction. The fast conversion time of the
AD7575 ensures that the microprocessor is not placed in a
WAIT state for an excessive amount of time.
TIMING AND CONTROL OF THE AD7575
The two logic inputs on the AD7575, CS and RD, control both
the starting of conversion and the reading of data from the part.
A conversion is initiated by bringing both of these control inputs
LOW. Two interface options then exist for reading the output
data from the AD7575. These are the Slow Memory Interface
and ROM Interface, their operation is outlined below. It should
be noted that the TP pin of the AD7575 must be hard-wired
HIGH to ensure correct operation of the part. This pin is used
in testing the device and should not be used as a feedthrough pin
in double-sided printed circuit boards.
Faster versions of many processors, including the 8085A-2, test
the condition of the READY input very soon after the start of
an instruction cycle. Therefore, BUSY of the AD7575 must go
LOW very early in the cycle for the READY input to be effec-
tive in forcing the processor into a WAIT state. When using the
8085A-2, the processor S0 status signal provides the earliest
possible indication that a READ operation is about to occur.
Hence, S0 (which is LOW for a READ cycle) provides the
READ signal to the AD7575. The connection diagram for the
AD7575 to 8085A-2 Slow Memory interface is shown in
Figure 4.
SLOW MEMORY INTERFACE
The first interface option is intended for use with microproces-
sors that can be forced into a WAIT STATE for at least 5 µs.
The microprocessor (such as the 8085A) starts a conversion and
is halted until the result of the conversion is read from the con-
verter. Conversion is initiated by executing a memory READ to
the AD7575 address, bringing CS and RD LOW. BUSY subse-
quently goes LOW (forcing the microprocessor READY input
LOW), placing the processor into a WAIT state. The input
signal, which had been tracked by the analog input, is held on
the third falling clock edge of the input clock after CS and RD
have gone LOW (see Figure 12). The AD7575 then performs a
conversion on this acquired input signal value. When the con-
version is complete (BUSY goes HIGH), the processor com-
pletes the memory READ and acquires the newly converted
data. The timing diagram for this interface is shown in Figure 3.
ROM INTERFACE
The alternative interface option on the AD7575 avoids placing
the microprocessor into a WAIT state. In this interface, a con-
version is started with the first READ instruction, and the sec-
ond READ instruction accesses the data and starts a second
conversion. The timing diagram for this interface is shown in
Figure 5. It is possible to avoid starting another conversion on
the second READ (see below).
Conversion is initiated by executing a memory READ instruc-
tion to the AD7575 address, causing CS and RD to go LOW.
Data is also obtained from the AD7575 during this instruction.
This is old data and may be disregarded if not required. BUSY
goes LOW, indicating that conversion is in progress, and re-
turns HIGH when conversion is complete. Once again, the
input signal is held on the third falling edge of the input clock
after CS and RD have gone LOW.
A8–A15
ADDRESS BUS
+5V
TP
8085A–2
ADDRESS
DECODE
CS
The BUSY line may be used to generate an interrupt to the
microprocessor or monitored to indicate that conversion is
complete. The processor then reads the newly-converted data.
Alternatively, the delay between the convert start (first READ
instruction) and the data READ (second READ instruction)
must be at least as great as the AD7575 conversion time. For
the AD7575 to operate correctly in the ROM interface mode,
CS and RD should not go LOW before BUSY returns HIGH.
AD7575*
S0
RD
BUSY
ADDRESS
LATCH
ALE
DB0–DB7
AD0–AD7
READY
DATA BUS
Normally, the second READ instruction starts another conver-
sion as well as accessing the output data. However, if CS and
RD are brought LOW within one external clock period of
BUSY going HIGH, a second conversion does not occur.
*LINEAR CIRCUITRY OMITTED FOR CLARITY
SO = 0 FOR READ CYCLES
Figure 4. AD7575 to 8085A-2 Slow Memory Interface
REV. B
–5–
AD7575
CS
RD
t1
t5
t4
t8
t2
BUSY
t3
t3
t7
t7
HIGH
IMPEDANCE BUS
OLD
DATA
HIGH IMPEDANCE
BUS
NEW
DATA
HIGH IMPEDANCE
BUS
DATA
Figure 5. ROM Interface Timing Diagram
Figures 6 and 7 show connection diagrams for interfacing the
AD7575 in the ROM Interface mode. Figure 6 shows the
AD7575 interface to the 6502/6809 microprocessors while the
connection diagram for interfacing to the Z-80 is shown in
Figure 7.
ADDRESS BUS
A0–A15
+5V
6502/6809
TP
ADDRESS
DECODE
EN
R/W
CS
RD
AD7575*
As a result of its very fast interface timing, the AD7575 can also
be interfaced to the DSP processor, the TMS32010. The
AD7575 will (within specifications) interface to the TMS32010,
running at up to 18 MHz, but will typically work over the full
clock frequency range of the TMS32010. Figure 8 shows the
connection diagram for this interface. The AD7575 is mapped
at a port address. Conversion is initiated using an IN A, PA
instruction where PA is the decoded port address for the
AD7575. The conversion result is obtained from the part using
a second IN A, PA instruction, and the resultant data is placed
in the TMS32010 accumulator.
2 OR E
DB0–DB7
DATA BUS
D0–D7
*LINEAR CIRCUITRY OMITTED FOR CLARITY
Figure 6. AD7575 to 6502/6809 ROM Interface
In many applications it is important that the signal sampling
occurs at exactly equal intervals to minimize errors due to sam-
pling uncertainty or jitter. The interfaces outlined previously
require that for sampling at equidistant intervals, the user must
count clock cycles or match software delays. This is especially
difficult in interrupt-driven systems where uncertainty in inter-
rupt servicing delays would require that the AD7575 have prior-
ity interrupt status and even then redundant software delays
may be necessary to equalize loop delays.
ADDRESS BUS
+5V
Z–80
TP
ADDRESS
DECODE
MREQ
RD
CS
EN
AD7575*
RD
DB7
DB0
DB7
DB0
This problem can be overcome by using a real time clock to
control the starting of conversion. This can be derived from the
clock source used to drive the AD7575 CLK pin. Since the
sampling instant occurs three clock cycles after CS and RD go
LOW, the input signal sampling intervals are equidistant. The
resultant data is placed in a FIFO latch that can be accessed by
the microprocessor at its own rate whenever it requires the data.
This ensures that data is not READ from the AD7575 during a
conversion. If a data READ is performed during a conversion,
valid data from the previous conversion will be accessed, but the
conversion in progress may be interfered with and an incorrect
result is likely.
DATA BUS
*LINEAR CIRCUITRY OMITTED FOR CLARITY
Figure 7. AD7575 to Z-80 ROM Interface
PA2
ADDRESS BUS
PA0
TMS32010
+5V
TP
ADDRESS
DECODE
MEN
DEN
EN
CS
AD7575*
If CS and RD go LOW within 20 ns of a falling clock edge, the
AD7575 may or may not see that falling edge as the first of the
three falling clock edges to the sampling instant. In this case, the
sampling instant could vary by one clock period. If it is impor-
tant to know the exact sampling instant, CS and RD should not
go LOW within 20 ns of a falling clock edge.
RD
DB7
DB0
D7
D0
DATA BUS
*LINEAR CIRCUITRY OMITTED FOR CLARITY
Figure 8. AD7575 to TMS32010 ROM Interface
REV. B
–6–
AD7575
A SAMPLED-DATA INPUT
40
42
44
46
48
50
52
54
T
= +25؇C
The AD7575 makes use of a sampled-data comparator. The
equivalent input circuit is shown in Figure 9. When a conversion
starts, switch S1 is closed, and the equivalent input capacitance
is charged to VIN. With a switch resistance of typically
500 Ω and an input capacitance of typically 2 pF, the input time
constant is 1 ns. Thus CIN becomes charged to within ±1/4 LSB
in 6.9 time constants or about 7 ns. Since the AD7575 requires
two input clock cycles (at a clock frequency of 4 MHz) before
going into the compare mode, there is ample time for the input
voltage to settle before the first comparator decision is made.
Increasing the source resistance increases the settling time re-
quired. Input bypass capacitors placed directly at the analog
input act to average the input charging currents. The average
current flowing through any source impedance can cause
full-scale errors.
A
100
1k
10k
100k
INPUT FREQUENCY – Hz
Figure 11. SNR vs. Input Frequency
R
ON
S1
500⍀
V
IN
The input signal is held on the third falling edge of the input
clock after CS and RD go LOW. This is indicated in Figure 12
for the Slow Memory Interface. Between conversions, the input
signal is tracked by the AD7575 track-and-hold. Since the
sampled signal is held on a small, on-chip capacitor, it is advis-
able that the data bus be kept as quiet as possible during a
conversion.
C
S
2pF
0.5pF
Figure 9. Equivalent Input Circuit
REFERENCE INPUT
The reference input impedance on the AD7575 is code depen-
dent and varies by a ratio of approximately 3-to-1 over the digi-
tal code range. The typical resistance range is from 6 kΩ to 18 kΩ.
As a result of the code dependent input impedance, the VREF
input must be driven from a low impedance source. Figure 10
shows how an AD589 can be configured to produce a nominal
reference voltage of +1.23 V.
CS
RD
BUSY
+5V
EXTERNAL
CLOCK
3.3k⍀
1.23V
INPUT SIGNAL
HELD HERE
+
47F
0.1F
AD589
–
Figure 12a. Track-and-Hold (Slow Memory Interface) with
External Clock
Figure 10. Reference Circuit
CS
RD
TRACK-AND-HOLD
The on-chip track-and-hold on the AD7575 means that input
signals with slew rates up to 386 mV/µs can be converted with-
out error. This corresponds to an input signal bandwidth of
50 kHz for a 2.46 V peak-to-peak sine wave. Figure 11 shows
a typical plot of signal-to-noise ratio versus input frequency over
the input bandwidth of the AD7575. The SNR figures are gen-
erated using a 200 kHz sampling frequency, and the reconstructed
sine wave passes through a filter with a cutoff frequency
of 50 kHz.
BUSY
INTERNAL
CLOCK
INPUT SIGNAL
HELD HERE
The improvement in the SNR figures seen at the higher frequen-
cies is due to the sharp cutoff of the filter (50 kHz, 8th
order Chebyshev) used in the test circuit.
Figure 12b. Track-and-Hold (Slow Memory Interface) with
Internal Clock
REV. B
–7–
AD7575
INTERNAL/EXTERNAL CLOCK
EXTERNAL CLOCK
The AD7575 can be used with its own internal clock or with an
externally applied clock. In either case, the clock signal appear-
ing at the CLK pin is divided internally by two to provide an
internal clock signal for the AD7575. A single conversion lasts
for 20 input clock cycles (10 internal clock cycles).
The CLK input of the AD7575 may be driven directly from
74 HC, 4000B series buffers (such as 4049) or from LS TTL
with a 5.6 kΩ pull-up resistor. When conversion is complete, the
internal clock is disabled even if the external clock is still ap-
plied. This means that the external clock can continue to run
between conversions without being disabled. The mark/space
ratio of the external clock can vary from 70/30 to 30/70.
INTERNAL CLOCK
Clock pulses are generated by the action of the external capaci-
tor (CCLK) charging through an external resistor (RCLK) and
discharging through an internal switch. When a conversion is
complete, the internal clock stops operating. In addition to
conversion, the internal clock also controls the automatic inter-
nal reset of the SAR. This reset occurs at the start of each con-
version cycle during the first internal clock pulse.
The AD7575 is specified for operation at a 5 µs conversion rate;
with a 4 MHz input clock frequency. If the part is operated at
slower clock frequencies, it may result in slightly degraded accu-
racy performance from the part. This is a result of leakage ef-
fects on the hold capacitor. Figure 14 shows a typical plot of
accuracy versus conversion time for the AD7575.
Nominal conversion times versus temperature for the recom-
mended RCLK and CCLK combination are shown in Figure 13.
2.5
T
= +25؇C
A
2.0
1.5
1.0
14
R
C
= 100k⍀
= 100pF
CLK
CLK
13
12
11
AD7575KN
10
0.5
0
9
8
7
5
10
50 100
500 1000
CONVERSION TIME – s
5000 10000
Figure 14. Accuracy vs. Conversion Time
–55
–25
0
+25
+50
+75
+100
+125
AMBIENT TEMPERATURE – ؇C
Figure 13. Typical Conversion Times vs. Temperature
Using Internal Clock
The internal clock is useful because it provides a convenient
clock source for the AD7575. Due to process variations, the
actual operating frequency for this RCLK/CCLK combination can
vary from device to device by up to ±50%. For this reason it is
recommended that an external clock be used in the following
situations:
1. Applications requiring a conversion time that is within 50% of
5 µs, the minimum conversion time for specified accuracy. A
clock frequency of 4 MHz at the CLK pin gives a conversion
time of 5 µs.
2. Applications where time related software constraints cannot
accommodate time differences that may occur due to unit to
unit clock frequency variations or temperature.
REV. B
–8–
AD7575
UNIPOLAR OPERATION
BIPOLAR OPERATION
The basic operation for the AD7575 is in the unipolar single
supply mode. Figure 15 shows the circuit connections to achieve
this, while the nominal transfer characteristic for unipolar opera-
tion is given in Figure 16. Since the offset and full-scale errors
on the AD7575 are very small, in many cases it will not be nec-
essary to adjust out these errors. If calibration is required, the
procedure is as follows:
The circuit of Figure 17 shows how the AD7575 can be config-
ured for bipolar operation. The output code provided by the
AD7575 is offset binary. The analog input voltage range is
±5 V, although the voltage appearing at the AIN pin of the
AD7575 is in the range 0 V to +2.46 V. Figure 18 shows the
transfer function for bipolar operation. The LSB size is now
39.06 mV. Calibration of the bipolar operation is outlined be-
low. Once again, because the errors are small, it may not be
necessary to adjust them. To maintain specified performance
without the calibration, all resistors should be 0.1% tolerance
with R4 and R5 replaced by one 3.3 kΩ resistor and R2 and R3
replaced by one 2.5 kΩ resistor.
Offset Adjust
Offset error adjustment in single-supply systems is easily achiev-
able by means of the offset null facility of an op amp when used
as a voltage follower for the analog input signal, AIN. The op
amp chosen should be able to operate from a single supply and
allow a common-mode input voltage range that includes 0 V
(e.g., TLC271). To adjust for zero offset, the input signal
source is set to +4.8 mV (i.e., 1/2 LSB) while the op amp offset
is varied until the ADC output code flickers between 000 . . . 00
and 000 . . . 01.
Offset Adjust
Offset error adjustment is achieved by applying an analog input
voltage of –4.9805 V (–FS +1/2 LSB). Resistor R3 is then
adjusted until the output code flickers between 000 . . . 00 and
000 . . . 01.
Full-Scale Adjust
Full-Scale Adjust
The full scale or gain adjustment is made by forcing the analog
input AIN to +2.445 V (i.e., Full-Scale Voltage –3/2 LSB). The
magnitude of the reference voltage is then adjusted until the
ADC output code flickers between 111 . . . 10 and 111. . . 11.
Full-scale or gain adjustment is made by applying an analog
input voltage of +4.9414 V (+FS –3/2 LSB). Resistor R4 is then
adjusted until the output code flickers between 111 . . . 10 and
111. . . 11.
+5V
+
+5V
47F
0.1F
+5V
47F
0.1F
+5V
A
A
+5V
A
A
R
CLK
R8
3.3k⍀
R
100k⍀, 1%
CLK
V
DD
100k⍀, 1%
V
CLK
V
REF
DD
C
+
CLK
CLK
47F
0.1F
R2
2.2k⍀
+5V
3.3k⍀
C
100pF, 2%
CLK
AD589
+2.46V
MAX
AIN
BUSY
100pF, 2%
D
–
D
A
A
BUSY
AD7575
CS
RD
TP
A
R3
500⍀
+5V
AD7575
+1.23V
0.1F
CS
RD
TP
CONTROL
INPUT
VOLTAGE
V
REF
+
INPUTS
47F
R1
10k⍀
TLC271
A
AIN
+5V
AD589
+5V
–
A
A
DB7–DB0
DATA OUT
A
R4
500⍀
AGND
AGND
DGND
DB7–DB0
DATA OUT
A
DGND
R7
2.5k⍀
R5
3k⍀
R6
2.5k⍀
A
D
D
A
A
Figure 15. Unipolar Configuration
Figure 17. Bipolar Configuration
OUTPUT
CODE
OUTPUT
FULL SCALE
CODE
TRANSITION
111...111
11111111
11111110
11111101
111...110
100...010
100...001
100...000
011...111
011...110
–1/2LSB
–FS
FS = 2V
1LSB =
REF
AIN
+FS –1LSB
FS
256
00000011
00000010
+1/2LSB
FS = 5V
FS
256
00000001
00000000
1LSB =
1LSB 3LSBs
2LSBs
FS
FS –1LSB
000...001
000...000
AIN, INPUT VOLTAGE (IN TERMS OF LSBs)
Figure 16. Nominal Transfer Characteristic for
Unipolar Operation
Figure 18. Nominal Transfer Characteristic for
Bipolar Operation
REV. B
–9–
AD7575
APPLICATION HINTS
The error analysis over temperature of ratiometric applications
is different from nonratiometric ones. Since the reference and
analog input voltage range are ratioed to each other, tempera-
ture variations in the reference are matched by variations in the
analog input range. Therefore, the AD589 contributes no addi-
tional errors over temperature to the system errors, and the
combined total unadjusted error specification for the AD589
and AD7575 is as per the total unadjusted error specification in
this data sheet.
1. NOISE: Both the input signal lead to AIN and the signal
return lead from AGND should be kept as short as possible to
minimize input-noise coupling. In applications where this is
not possible, either a shielded cable or a twisted pair transmis-
sion line between source and ADC is recommended. Also,
since any potential difference in grounds between the signal
source and ADC appears as an error voltage in series with the
input signal, attention should be paid to reducing the ground
circuit impedance as much as possible. In general, the source
resistance should be kept below 2 kΩ. Larger values of source
resistance can cause undesired system noise pickup.
With nonratiometric applications, however, the analog input
range stays the same if the reference varies and a full-scale error
is introduced. The amount by which the reference varies deter-
mines the amount of error introduced. The AD589 is graded on
temperature coefficient; therefore, selection of different grades
allows the user to tailor the amount of error introduced to suit
the system requirements. The reference voltage from the AD589
can lie between 1.2 V and 1.25 V. This reference voltage can be
adjusted for the desired full-scale voltage range using the circuit
outlined in Figure 19. For example, if an analog input voltage
range of 0 V to +2.46 V is required, the reference should be
adjusted to +1.23 V. Once the reference is adjusted to the de-
sired value at 25°C, the total error is as per the total unadjusted
error specification on the AD7575 specification pages. (To
reduce this still further, offset and full-scale errors of the
AD7575 can be adjusted out using the calibration procedure
outlined in this data sheet.)
2. PROPER LAYOUT: Layout for a printed circuit board
should ensure that digital and analog lines are kept separated
as much as possible. In particular, care should be taken not to
run any digital track alongside an analog signal track. Both the
analog input and the reference input should be screened by
AGND. A single point analog ground separate from the logic
system ground, should be established at or near the AD7575.
This single point analog ground subsystem should be con-
nected to the digital system ground by a single-track connec-
tion only. Any reference bypass capacitors, analog input filter
capacitors or input signal shielding should be returned to the
analog ground point.
AD7575 WITH AD589 REFERENCE
The AD7575 8-bit A/D converter features a total unadjusted
error specification over its entire operating temperature range.
This total unadjusted error includes all errors in the A/D con-
verter—offset, full scale and linearity. The one feature not pro-
vided on the AD7575 is a voltage reference. This section
discusses the use of the AD589 bandgap reference with the
AD7575, and gives the combined reference and ADC error
budget over the full operating temperature range. This allows
the user to compare the combined AD589/AD7575 errors to
ADCs whose specifications include on-chip references.
+5V
10k⍀*
1k⍀*
+5V
6.8k⍀
TLC271*
+
–
10k⍀*
AD589
*ONLY REQUIRED IF IT IS NECESSARY TO ADJUST
THE ABSOLUTE VALUE OF REFERENCE VOLTAGE.
Two distinct application areas exist. The first is where the refer-
ence voltage and the analog input voltage are derived from the
same source. In other words, if the reference voltage varies, the
analog input voltage range varies by a ratioed amount. In this
case, the user is not worried about the absolute value of the
reference voltage. The second case is where changes in the refer-
ence voltage are not matched by changes in the analog input
voltage range. Here, the absolute value of the reference voltage,
and its drift over temperature, are of prime importance. Both
applications are discussed below.
Figure 19. Reference Adjust Circuit
However, it is as the temperature varies from 25°C that the
AD589 starts to introduce errors. The typical temperature char-
acteristics of the AD589 are shown in Figure 20. The tempera-
ture coefficients (TCs) represent the slopes of the diagonals of
the error band from +25°C to TMIN and +25°C to TMAX. The
AD589 TC is specified in ppm/°C max and is offered in four
different grades.
If the analog input range varies with the reference voltage, the
part is said to be operating ratiometrically. This is representative
of many applications. If the reference is on-chip, and the user
does not have access to it, it is not possible to get ratiometric
operation. Since the AD7575 uses an external reference, it can
be used in ratiometric applications. However, because the part is
specified with a reference of +1.23 V ± 5%, then the voltage
range for ratiometric operation is limited.
REV. B
–10–
AD7575
Taking the 25°C measurement as the starting point, the
1.2370
1.2365
1.2360
1.2355
1.2350
1.2345
full-scale error introduced is always in the negative direction
whether the temperature goes to TMIN or TMAX. This can be
seen from the AD589 temperature characteristic shown in Fig-
ure 20. If the reference voltage is adjusted for 1.23 V at 45°C
(for the 0°C to +70°C range) and 75°C (for the –55°C to
+125°C range) the magnitude of the error introduced is reduced
since it is distributed in both the positive and negative direc-
tions. Alternatively, this can be achieved not by adjusting at
these temperatures, which would be impractical, but by adjust-
ing the reference to 1.231 V instead of 1.23 V (for the extended
temperature range) at 25°C. This has the required effect of
distributing the plot of Figure 20 more evenly about the desired
value.
–50
–25
0
25
50
75
100
125
An additional error source is the mismatch between the tem-
perature coefficients (TCs) of the 10 kΩ and 1 kΩ resistors in
the feedback loop of the TLC271. If these resistors have
±50 ppm/°C absolute TCs, the worst case difference in drift be-
tween both resistors is 100 ppm/°C. From +25°C to +125°C, this
introduces a worst case shift of 1.22 mV, which results in an addi-
tional full-scale error of 0.25 LSB. If ±25 ppm/°C resistors are
used, then the worst case error is 0.13 LSB. Over the 0°C to
+70°C range, the ±50 ppm/°C resistors introduce an additional
full-scale error of 0.11 LSB. All these errors are worst case and
assume that the resistance values drift in opposite directions. In
practice, resistors of the same type, and from the same manufac-
turer, would drift in the same direction and hence the above
error would be considerably reduced. An additional error source
is the offset drift of the TLC271. This is significant only over
the –55°C to +125°C range and, even in this case, it contrib-
utes <0.1 LSB worth of full-scale error.
TEMPERATURE – ؇C
Figure 20. Typical AD589 Temperature Characteristics
The effect the TC has on the system error is that it introduces a
full-scale error in the ADC. This, in turn, affects the total unad-
justed error specification. For example, using the AD589KH
with a 50 ppm/°C max TC the change in reference voltage from
25°C to 70°C will be from 1.23 V to 1.22724 V, a change of –
2.76 mV. This results in a change in the full-scale range of the
ADC of –5.52 mV, since the full-scale range on the AD7575 is
2 VREF. Because the LSB size for the AD7575 is 9.61 mV, the
AD589 introduces an additional full-scale error of –0.57 LSBs
on top of the existing full-scale error specification for the ADC.
Since the total unadjusted error specification for the ADC
includes the full-scale error, there is also a corresponding in-
crease in the total unadjusted error of –0.57 LSBs. The change
in reference voltage at 0°C is –1.5 mV, resulting in a full-scale
change of –3 mV or –0.31 LSBs worth of full-scale error. Table I
shows the amount of additional total unadjusted error, which is
introduced by the temperature variation of the AD589, for
different grades and for different temperature ranges. This table
applies only to nonratiometric applications, because the tem-
perature variation of the reference does not affect the system
error in ratiometric applications as outlined earlier. It shows the
amount of error introduced over TMIN to TMAX for a system in
which the reference has been adjusted to the desired value at
25°C. The final or right-most column of the table gives the total
combined error for the AD589 and the top grade AD7575.
The error outlined in the right-hand column of Table I is a total
unadjusted error specification, excluding resistor and offset drift
(the effect of these can be controlled by the user). It consists of
errors from two error sources: a ±l LSB contribution from the
AD7575 (including full-scale, offset and relative accuracy er-
rors), and the remainder is a full-scale error introduced by the
AD589. It is important to note that the variation of the AD589
voltage only introduces a full-scale error; the relative accuracy
(or endpoint nonlinearity) of the system, with a top grade
AD7575, is still ±1/2 LSB (i.e., 8-bits accurate).
Table I. AD589/AD7575 Error over Temperature (Nonratiometric Applications)
Full-Scale Error Introduced
by AD589 @ TMAX
(Worst Case)
Combined Worst Case
AD589/AD7575
T.U.E. @ TMAX
AD589
Grade
Temperature
Range
AD589JH
AD589KH
AD589LH
AD589MH
AD589SH
AD589TH
AD589UH
0°C to +70°C
0°C to +70°C
0°C to +70°C
0°C to +70°C
–55°C to +125°C
–55°C to +125°C
–55°C to +125°C
–1.15 LSB
–0.57 LSB
–0.29 LSB
–0.115 LSB
–2.56 LSB
–1.28 LSB
–0.64 LSB
–2.15 LSB
–1.57 LSB
–1.29 LSB
–1.115 LSB
–3.56 LSB
–2.28 LSB
–1.64 LSB
*Excluding resistor and offset drift.
REV. B
–11–
AD7575
OUTLINE DIMENSIONS
Dimensions shown in inches and (mm).
18-Lead Plastic DIP
(N-18)
20-Lead PLCC
(P-20A)
0.91 (23.12)
0.89 (22.61)
0.173 ؎0.008
(4.388 ؎0.185)
0.353 ؎0.003
(8.966 ؎0.076)
0.020
(0.51)
SQ
MIN
18
1
10
9
0.26 (6.61)
0.24 (6.10)
0.035 ؎0.01
(0.89 ؎0.25)
0.045 ؎0.003
(1.143 ؎0.076)
R
3
19
18
0.306 (7.78)
0.294 (7.47)
4
8
PIN 1
0.029 ؎0.003
(0.737 ؎0.076)
IDENTIFIER
0.050
(1.27)
PIN 1
TOP VIEW
(PINS DOWN)
0.175 (4.45)
0.12 (3.05)
0.18
(4.58)
MAX
0.14 (3.56)
0.12 (3.05)
0.017 ؎0.004
(0.432 ؎0.101)
14
13
9
0.020
(0.51)
MAX
15؇
0.025
MIN
0
(0.64)
0.390 ؎0.005
(9.905 ؎0.125)
0.12 (0.305)
SQ
0.02 (0.508) 0.105 (2.67)
0.015 (0.381) 0.095 (2.42)
0.065 (1.66)
0.045 (1.15)
0.105 ؎0.015
(2.665 ؎0.375)
0.008 (0.203)
SEATING
PLANE
18-Lead Cerdip
(Q-18)
20-Terminal LCCC
(E-20A)
0.082 ؎ 0.018
(2.085 ؎ 0.455)
0.350 ؎ 0.008
(8.89 ؎ 0.20)
18
10
SQ
0.020
؋
45؇ (0.51
؋
45؇) 0.310 (7.874)
0.260 (6.604)
REF
1
9
3
19
18
20
0.320 (8.128)
0.290 (7.366)
4
PIN 1
0.950 (24.13) MAX
0.025 ؎ 0.003
(0.635 ؎ 0.075)
1
0.060 (1.524)
0.015 (0.381)
BOTTOM
VIEW
0.180 (4.572)
14
13
8
0.140 (3.556)
0.015 (0.381)
0.008 (0.203)
9
0.040
؋
45؇ (1.02
؋
45؇) REF 3 PLCS
0.200 (5.080)
0.125 (3.175)
0.050
(1.27)
0.070 (1.778)
0.030 (0.762)
0.023 (0.584) 0.110 (2.794)
0.015 (0.381) 0.090 (2.286)
0.400 (10.160)
0.330 (8.382)
SEATING
PLANE
18-Lead SOIC
(R-18)
0.4625 (11.75)
0.4469 (11.35)
18
10
1
9
PIN 1
0.1043 (2.65)
0.0926 (2.35)
0.0291 (0.74)
؋
45؇ 0.0098 (0.25)
0.0500 (1.27)
8؇
0؇ 0.0157 (0.40)
0.0500
(1.27)
BSC
0.0192 (0.49)
0.0118 (0.30)
0.0040 (0.10)
SEATING
PLANE
0.0125 (0.32)
0.0091 (0.23)
0.0138 (0.35)
REV. B
–12–
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