AD7675 [ADI]
16-Bit, 100 kSPS, Differential ADC; 16位100 kSPS时，差分ADC
| 型号： | AD7675 |
| 厂家： | 
ADI |
| 描述： | 16-Bit, 100 kSPS, Differential ADC |
| 文件： | 总20页 (文件大小：394K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
16-Bit, 100 kSPS,
Differential ADC
a
AD7675*
FEATURES
FUNCTIONAL BLOCK DIAGRAM
Throughput: 100 kSPS
AVDD AGND REF REFGND
DVDD DGND
INL: ؎1.5 LSB Max (؎0.0015% of Full-Scale)
16 Bits Resolution with No Missing Codes
S/(N+D): 94 dB Typ @ 45 kHz
OVDD
OGND
AD7675
THD: –110 dB Typ @ 45 kHz
SERIAL
PORT
Differential Input Range: ؎2.5 V
Both AC and DC Specifications
No Pipeline Delay
Parallel (8/16 Bits) and Serial 5 V/3 V Interface
SPI™/QSPI™/MICROWIRE™/DSP Compatible
Single 5 V Supply Operation
15 mW Typical Power Dissipation, 15 W @ 100 SPS
Power-Down Mode: 7 W Max
Package: 48-Lead Quad Flat Pack (LQFP)
Pin-to-Pin Compatible with the AD7660
Replacement of AD676, AD677
IN+
IN–
SWITCHED
CAP DAC
SER/PAR
BUSY
DATA[15:0]
CS
16
PARALLEL
INTERFACE
CLOCK
PD
CONTROL LOGIC AND
CALIBRATION CIRCUITRY
RD
RESET
OB/2C
BYTESWAP
CNVST
APPLICATIONS
CT Scanners
Data Acquisition
Instrumentation
Spectrum Analysis
Medical Instruments
Battery-Powered Systems
Process Control
GENERAL DESCRIPTION
PRODUCT HIGHLIGHTS
The AD7675 is a 16-bit, 100 kSPS, charge redistribution SAR,
fully differential analog-to-digital converter that operates from a
single 5 V power supply. The part contains a high-speed 16-bit
sampling ADC, an internal conversion clock, error correction
circuits, and both serial and parallel system interface ports.
1. Excellent INL
The AD7675 has a maximum integral nonlinearity of 1.5 LSB
with no missing 16-bit code.
2. Superior AC Performances
The AD7675 has a minimum dynamic of 92 dB, 94 dB typical.
The AD7675 is hardware factory calibrated and is comprehensively
tested to ensure such ac parameters as signal-to-noise ratio (SNR)
and total harmonic distortion (THD), in addition to the more
traditional dc parameters of gain, offset, and linearity.
3. Fast Throughput
The AD7675 is a 100 kSPS, charge redistribution, 16-bit
SAR ADC with internal error correction circuitry.
4. Single-Supply Operation
It is fabricated using Analog Devices’ high-performance, 0.6
micron CMOS process and is available in a 48-lead LQFP with
operation specified from –40°C to +85°C.
The AD7675 operates from a single 5 V supply and typically
dissipates only 17 mW. Its power dissipation decreases
with the throughput to, for instance, only 15 µW at a 100 SPS
throughput. It consumes 7 µW maximum when in power-down.
5. Serial or Parallel Interface
Versatile parallel (8 or 16 bits) or 2-wire serial interface
arrangement compatible with either 3 V or 5 V logic.
*Patent pending
SPI and QSPI are trademarks of Motorola Inc.
MICROWIRE is a trademark of National Semiconductor Inc.
REV. 0
Information furnished by Analog Devices is believed to be accurate and
reliable. However, no responsibility is assumed by Analog Devices for its
use, norforanyinfringementsofpatentsorotherrightsofthirdpartiesthat
may result from its use. No license is granted by implication or otherwise
under any patent or patent rights of Analog Devices.
One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A.
Tel: 781/329-4700
Fax: 781/326-8703
www.analog.com
© Analog Devices, Inc., 2001
AD7675–SPECIFICATIONS (–40؇C to +85؇C, AVDD = DVDD = 5 V, OVDD = 2.7 V to 5.25 V, unless otherwise noted.)
Parameter
Conditions
Min
Typ
Max
Unit
RESOLUTION
16
Bits
ANALOG INPUT
Voltage Range
Operating Input Voltage
Analog Input CMRR
Input Current
VIN+ – VIN–
VIN+, VIN– to AGND
–VREF
–0.1
+VREF
+3
V
V
dB
µA
f
IN = 10 kHz
79
1
100 kSPS Throughput
Input Impedance
See Analog Input Section
0
THROUGHPUT SPEED
Complete Cycle
Throughput Rate
10
100
µs
kSPS
DC ACCURACY
Integral Linearity Error
No Missing Codes
Transition Noise
–1.5
16
+1.5
LSB1
Bits
LSB
LSB
LSB
LSB
LSB
0.35
0.5
+Full-Scale Error2
–Full-Scale Error2
Zero Error2
–22
–22
–8
+22
+22
+8
Power Supply Sensitivity
AVDD = 5 V 5%
AC ACCURACY
Signal-to-Noise
fIN = 20 kHz
fIN = 45 kHz
fIN = 20 kHz
fIN = 45 kHz
fIN = 20 kHz
fIN = 45 kHz
fIN = 20 kHz
fIN = 45 kHz
92
94
94
110
110
–110
–110
94
94
34
3.9
dB3
dB3
dB3
dB3
dB3
dB3
dB3
dB3
dB3
MHz
Spurious Free Dynamic Range
Total Harmonic Distortion
Signal-to-(Noise+Distortion)
104.5
–103.5
92
fIN = 45 kHz, –60 dB Input
–3 dB Input Bandwidth
SAMPLING DYNAMICS
Aperture Delay
Aperture Jitter
2
5
ns
ps rms
µs
Transient Response
Full-Scale Step
8.75
REFERENCE
External Reference Voltage Range
External Reference Current Drain
2.3
2.5
35
AVDD – 1.85
V
µA
100 kSPS Throughput
DIGITAL INPUTS
Logic Levels
VIL
VIH
IIL
–0.3
+2.0
–1
+0.8
DVDD + 0.3
+1
+1
V
V
µA
µA
IIH
–1
DIGITAL OUTPUTS
Data Format
Pipeline Delay
VOL
Parallel or Serial 16-Bit Conversion Results Available
Immediately After Completed Conversion
ISINK = 1.6 mA
ISOURCE = –100 µA
0.4
V
V
VOH
OVDD – 0.6
POWER SUPPLIES
Specified Performance
AVDD
4.75
4.75
2.7
5
5
5.25
5.25
5.25
V
V
V
DVDD
OVDD
Operating Current
AVDD
300 kSPS Throughput
3
mA
µA
DVDD4
750
7.5
17
15
OVDD4
µA
Power Dissipation4
100 kSPS Throughput
100 SPS Throughput
25
7
mW
µW
µW
In Power-Down Mode5
TEMPERATURE RANGE6
Specified Performance
TMIN to TMAX
–40
+85
°C
NOTES
1LSB means Least Significant Bit. With the 2.5 V input range, one LSB is 76.3 µV.
2See Definition of Specifications section. These specifications do not include the error contribution from the external reference.
3All specifications in dB are referred to a full-scale input FS. Tested with an input signal at 0.5 dB below full-scale unless otherwise specified.
4Tested in parallel reading mode.
5With all digital inputs forced to OVDD or OGND respectively.
6Contact factory for extended temperature range.
Specifications subject to change without notice.
–2–
REV. 0
AD7675
TIMING SPECIFICATIONS (–40؇C to +85؇C, AVDD = DVDD = 5 V, OVDD = 2.7 V to 5.25 V, unless otherwise noted.)
Symbol
Min
Typ
Max
Unit
Refer to Figures 11 and 12
Convert Pulsewidth
Time Between Conversions
CNVST LOW to BUSY HIGH Delay
BUSY HIGH All Modes Except in Master Serial Read
After Convert Mode
t1
t2
t3
t4
5
10
ns
µs
ns
µs
30
1.25
Aperture Delay
End of Conversion to BUSY LOW Delay
Conversion Time
Acquisition Time
RESET Pulsewidth
t5
t6
t7
t8
t9
2
ns
ns
µs
µs
ns
10
1.25
8.75
10
Refer to Figures 13, 14, and 15 (Parallel Interface Modes)
CNVST LOW to DATA Valid Delay
DATA Valid to BUSY LOW Delay
Bus Access Request to DATA Valid
Bus Relinquish Time
t10
t11
t12
t13
1.25
µs
ns
ns
ns
45
5
40
15
Refer to Figures 16 and 17 (Master Serial Interface Modes)1
CS LOW to SYNC Valid Delay
CS LOW to Internal SCLK Valid Delay
CS LOW to SDOUT Delay
t14
t15
t16
t17
t18
t19
t20
t21
t22
t23
t24
t25
t26
t27
t28
t29
t30
10
10
10
ns
ns
ns
ns
ns
ns
ns
ns
ns
ns
ns
ns
ns
ns
µs
µs
ns
CNVST LOW to SYNC Delay
SYNC Asserted to SCLK First Edge Delay2
Internal SCLK Period2
525
3
25
12
7
4
2
40
Internal SCLK HIGH2
Internal SCLK LOW2
SDOUT Valid Setup Time2
SDOUT Valid Hold Time2
SCLK Last Edge to SYNC Delay2
CS HIGH to SYNC HI-Z
3
10
10
10
CS HIGH to Internal SCLK HI-Z
CS HIGH to SDOUT HI-Z
BUSY HIGH in Master Serial Read After Convert2
CNVST LOW to SYNC Asserted Delay
SYNC Deasserted to BUSY LOW Delay
See Table I
1.25
25
Refer to Figures 18 and 19 (Slave Serial Interface Modes)
External SCLK Setup Time
External SCLK Active Edge to SDOUT Delay
SDIN Setup Time
SDIN Hold Time
External SCLK Period
t31
t32
t33
t34
t35
t36
t37
5
3
5
5
25
10
10
ns
ns
ns
ns
ns
ns
ns
18
External SCLK HIGH
External SCLK LOW
NOTES
1In serial interface modes, the SYNC, SCLK, and SDOUT timings are defined with a maximum load CL of 10 pF; otherwise, the load is 60 pF maximum.
2In serial master read during convert mode. See Table I for serial master read after convert mode.
Specifications subject to change without notice.
–3–
REV. 0
AD7675
Table I. Serial Clock Timings in Master Read after Convert
DIVSCLK[1]
DIVSCLK[0]
0
0
0
1
1
0
1
1
Unit
SYNC to SCLK First Edge Delay Minimum
Internal SCLK Period Minimum
Internal SCLK Period Typical
Internal SCLK HIGH Minimum
Internal SCLK LOW Minimum
SDOUT Valid Setup Time Minimum
SDOUT Valid Hold Time Minimum
SCLK Last Edge to SYNC Delay Minimum
Busy High Width Maximum
t18
t19
t19
t20
t21
t22
t23
t24
t28
3
17
50
70
22
21
18
4
17
17
ns
ns
ns
ns
ns
ns
ns
ns
µs
25
40
12
7
4
2
100
140
50
49
18
30
140
3.5
200
280
100
99
18
89
3
2
60
2.5
300
5.75
ABSOLUTE MAXIMUM RATINGS1
I
1.6mA
OL
Analog Inputs
IN+2, IN–2, REF, REFGND . . . . . . . . . . . . . . . . . . . . . . . .
. . . . . . . . . . . . . . . . . . . . AVDD + 0.3 V to AGND – 0.3 V
Ground Voltage Differences
AGND, DGND, OGND . . . . . . . . . . . . . . . . . . . . . 0.3 V
Supply Voltages
TO OUTPUT
PIN
1.4V
C
L
1
60pF
I
500A
OH
AVDD, DVDD, OVDD . . . . . . . . . . . . . . . . . . . . . . . . . 7 V
NOTE
1
AVDD to DVDD, AVDD to OVDD . . . . . . . . . . . . . .
DVDD to OVDD . . . . . . . . . . . . . . . . . . . . . . . . . . . .
7 V
7 V
IN SERIAL INTERFACE MODES,THE SYNC, SCLK, AND
SDOUT TIMINGS ARE DEFINEDWITH A MAXIMUM LOAD
C
OF 10pF; OTHERWISE,THE LOAD IS 60pF MAXIMUM.
L
Digital Inputs . . . . . . . . . . . . . . . . –0.3 V to DVDD + 0.3 V
Internal Power Dissipation3 . . . . . . . . . . . . . . . . . . . . 700 mW
Junction Temperature . . . . . . . . . . . . . . . . . . . . . . . . . 150°C
Storage Temperature Range . . . . . . . . . . . . –65°C to +150°C
Lead Temperature Range
Figure 1. Load Circuit for Digital Interface Timing, SDOUT,
SYNC, SCLK Outputs, CL = 10 pF
2V
(Soldering 10 sec) . . . . . . . . . . . . . . . . . . . . . . . . . . 300°C
0.8V
NOTES
tDELAY
tDELAY
1Stresses above those listed under Absolute Maximum Ratings may cause perma-
nent damage to the device. This is a stress rating only; functional operation of the
device at these or any other conditions above those indicated in the operational
section of this specification is not implied. Exposure to absolute maximum rating
conditions for extended periods may affect device reliability.
2See Analog Input section.
2V
2V
0.8V
0.8V
Figure 2. Voltage Reference Levels for Timing
3Specification is for device in free air: 48-Lead LQFP: JA = 91°C/W, JC = 30°C/W.
ORDERING GUIDE
Package
Option
Model
Temperature Range
Package Description
AD7675AST
–40°C to +85°C
–40°C to +85°C
Quad Flatpack (LQFP)
Quad Flatpack (LQFP)
Evaluation Board
ST-48
ST-48
AD7675ASTRL
EVAL-AD7675CB1
EVAL-CONTROL BRD22
Controller Board
NOTES
1This board can be used as a stand-alone evaluation board or in conjunction with the EVAL-CONTROL BRD2 for evaluation/
demonstration purposes.
2This board allows a PC to control and communicate with all Analog Devices evaluation boards ending in the CB designators.
CAUTION
ESD (electrostatic discharge) sensitive device. Electrostatic charges as high as 4000 V readily
accumulate on the human body and test equipment and can discharge without detection. Although
the AD7675 features proprietary ESD protection circuitry, permanent damage may occur on
devices subjected to high-energy electrostatic discharges. Therefore, proper ESD precautions are
recommended to avoid performance degradation or loss of functionality.
WARNING!
ESD SENSITIVE DEVICE
–4–
REV. 0
AD7675
PIN FUNCTION DESCRIPTIONS
Type Description
Pin No.
Mnemonic
1
2
AGND
AVDD
NC
P
P
Analog Power Ground Pin
Input Analog Power Pins. Nominally 5 V.
No Connect
3, 6, 7,
40–42,
44–48
4
BYTESWAP
DI
DI
Parallel Mode Selection (8/16 Bit). When LOW, the LSB is output on D[7:0] and the MSB is
output on D[15:8]. When HIGH, the LSB is output on D[15:8] and the MSB is output on D[7:0].
Straight Binary/Binary Two’s Complement. When OB/2C is HIGH, the digital output is
straight binary; when LOW, the MSB is inverted resulting in a two’s complement output
from its internal shift register.
5
OB/2C
8
SER/PAR
DI
Serial/Parallel Selection Input. When LOW, the parallel port is selected; when HIGH, the
serial interface mode is selected and some bits of the DATA bus are used as a serial port.
9, 10
11, 12
DATA[0:1]
DO
DI/O
Bit 0 and Bit 1 of the Parallel Port Data Output Bus. When SER/PAR is HIGH, these outputs are
in high impedance.
When SER/PAR is LOW, these outputs are used as Bit 2 and Bit 3 of the Parallel Port
Data Output Bus.
When SER/PAR is HIGH, EXT/INT is LOW and RDC/SDIN is LOW which is the serial
master read after convert mode. These inputs, part of the serial port, are used to slow down, if
desired, the internal serial clock which clocks the data output. In the other serial modes, these
inputs are not used.
DATA[2:3] or
DIVSCLK[0:1]
13
DATA[4]
DI/O
When SER/PAR is LOW, this output is used as the Bit 4 of the Parallel Port Data Output Bus.
or EXT/INT
When SER/PAR is HIGH, this input, part of the serial port, is used as a digital select input for
choosing the internal or an external data clock. With EXT/INT tied LOW, the internal clock
is selected on SCLK output. With EXT/INT set to a logic HIGH, output data is synchronized
to an external clock signal connected to the SCLK input.
14
15
16
DATA[5]
or INVSYNC
DI/O
DI/O
DI/O
When SER/PAR is LOW, this output is used as the Bit 5 of the Parallel Port Data Output Bus.
When SER/PAR is HIGH, this input, part of the serial port, is used to select the active state of
the SYNC signal. When LOW, SYNC is active HIGH. When HIGH, SYNC is active LOW.
When SER/PAR is LOW, this output is used as the Bit 6 of the Parallel Port Data Output Bus.
When SER/PAR is HIGH, this input, part of the serial port, is used to invert the SCLK signal.
It is active in both master and slave mode.
When SER/PAR is LOW, this output is used as the Bit 7 of the Parallel Port Data Output Bus.
DATA[6]
or INVSCLK
DATA[7]
or RDC/SDIN
When SER/PAR is HIGH, this input, part of the serial port, is used as either an external data
input or a read mode selection input depending on the state of EXT/INT.
When EXT/INT is HIGH, RDC/SDIN could be used as a data input to daisy chain the con-
version results from two or more ADCs onto a single SDOUTline. The digital data level on
SDIN is output on DATA with a delay of 16 SCLK periods after the initiation of the read
sequence. When EXT/INT is LOW, RDC/SDIN is used to select the read mode. When RDC/
SDIN is HIGH, the data is output on SDOUT during conversion. When RDC/SDIN is LOW,
the data is output on SDOUT only when the conversion is complete.
17
18
OGND
OVDD
P
P
Input/Output Interface Digital Power Ground
Input/Output Interface Digital Power. Nominally at the same supply than the supply of the
host interface (5 V or 3 V).
19
20
DVDD
DGND
P
P
Digital Power. Nominally at 5 V.
Digital Power Ground
REV. 0
–5–
AD7675
PIN FUNCTION DESCRIPTIONS (continued)
Pin No.
Mnemonic
Type
Description
21
DATA[8]
DO
When SER/PAR is LOW, this output is used as the Bit 8 of the Parallel Port Data Output Bus.
or SDOUT
When SER/PAR is HIGH, this output, part of the serial port, is used as a serial data output
synchronized to SCLK. Conversion results are stored in an on-chip register. The AD7675
provides the conversion result, MSB first, from its internal shift register. The DATA
format is determined by the logic level of OB/2C. In serial mode, when EXT/INT is LOW,
SDOUT is valid on both edges of SCLK. In serial mode, when EXT/INT is HIGH: If
INVSCLK is LOW, SDOUT is updated on SCLK rising edge and valid on the next falling
edge. If INVSCLK is HIGH, SDOUT is updated on SCLK falling edge and valid on the next
rising edge.
22
23
DATA[9]
or SCLK
DI/O
DO
When SER/PAR is LOW, this output is used as the Bit 9 of the Parallel Port Data Output Bus.
When SER/PAR is HIGH, this pin, part of the serial port, is used as a serial data clock input
or output, dependent upon the logic state of the EXT/INT pin. The active edge where the
data SDOUT is updated depends upon the logic state of the INVSCLK pin.
DATA[10]
or SYNC
When SER/PAR is LOW, this output is used as the Bit 10 of the Parallel Port Data Output Bus.
When SER/PAR is HIGH, this output, part of the serial port, is used as a digital output frame
synchronization for use with the internal data clock (EXT/INT = Logic LOW). When a read
sequence is initiated and INVSYNC is LOW, SYNC is driven HIGH and remains HIGH
while SDOUT output is valid. When a read sequence is initiated and INVSYNC is HIGH,
SYNC is driven LOW and remains LOW while SDOUT output is valid.
24
DATA[11]
DO
When SER/PAR is LOW, this output is used as the Bit 11 of the Parallel Port Data Output Bus.
or RDERROR
When SER/PAR is HIGH and EXT/INT is HIGH, this output, part of the serial port, is used
as an incomplete read error flag. In slave mode, when a data read is started and not complete
when the following conversion is complete, the current data is lost and RDERROR is pulsed high.
25–28
29
DATA[12:15]
BUSY
DO
DO
Bit 12 to Bit 15 of the Parallel Port Data output bus. These pins are always outputs regardless
of the state of SER/PAR.
Busy Output. Transitions HIGH when a conversion is started, and remains HIGH until the
conversion is complete and the data is latched into the on-chip shift register. The falling edge
of BUSY could be used as a data ready clock signal.
30
31
32
DGND
RD
P
DI
DI
Must be tied to digital ground.
Read Data. When CS and RD are both LOW, the interface parallel or serial output bus is enabled.
Chip Select. When CS and RD are both LOW, the interface parallel or serial output bus is
enabled. CS is also used to gate the external serial clock.
CS
33
34
RESET
PD
DI
DI
Reset Input. When set to a logic HIGH, reset the AD7675. Current conversion if any is aborted.
Power-Down Input. When set to a logic HIGH, power consumption is reduced and conver-
sions are inhibited after the current one is completed.
35
CNVST
DI
Start Conversion. If CNVST is HIGH when the acquisition phase (t8) is complete, the next
falling edge on CNVST puts the internal sample/hold into the hold state and initiates a
conversion. This mode is the most appropriate if low sampling jitter is desired. If CNVST is
LOW when the acquisition phase (t8) is complete, the internal sample/hold is put into the hold
state and a conversion is immediately started.
36
37
38
39
AGND
REF
REFGND
IN–
P
Must be tied to analog ground.
Reference Input Voltage
Reference Input Analog Ground
Differential Negative Analog Input
Differential Positive Analog Input
AI
AI
AI
AI
43
IN+
NOTES
AI = Analog Input
DI = Digital Input
DI/O = Bidirectional Digital
DO = Digital Output
P = Power
–6–
REV. 0
AD7675
PIN CONFIGURATION
48-Lead LQFP
(ST-48)
48 47 46 45 44 43 42 41 40 39 38 37
1
2
AGND
AVDD
36
35
34
33
32
31
30
29
28
27
26
25
AGND
PIN 1
IDENTIFIER
CNVST
PD
3
NC
4
BYTESWAP
RESET
5
OB/2C
NC
CS
AD7675
6
RD
TOPVIEW
7
NC
DGND
BUSY
D15
D14
D13
D12
(Not to Scale)
8
SEP/PAR
D0
9
10
11
12
D1
D2/DIVSCLK[0]
D3/DIVSCLK[1]
13 14 15 16 17 18 19 20 21 22 23 24
NC = NO CONNECT
EFFECTIVE NUMBER OF BITS (ENOB)
ENOB is a measurement of the resolution with a sine wave
input. It is related to S/(N+D) by the following formula:
DEFINITION OF SPECIFICATIONS
INTEGRAL NONLINEARITY ERROR (INL)
Integral Nonlinearity is the maximum deviation of a straight line
drawn through the transfer function of the actual ADC. The
deviation is measured from the middle of each code.
ENOB = S / N + D
–1.76 / 6.02
[
(
]
)
dB
and is expressed in bits.
DIFFERENTIAL NONLINEARITY ERROR (DNL)
In an ideal ADC, code transitions are 1 LSB apart. Differential
nonlinearity is the maximum deviation from this ideal value. It
is often specified in terms of resolution for which no missing
codes are guaranteed.
TOTAL HARMONIC DISTORTION (THD)
THD is the ratio of the rms sum of the first five harmonic
components to the rms value of a full-scale input signal and is
expressed in decibels.
+FULL-SCALE ERROR
SIGNAL-TO-NOISE RATIO (SNR)
The last transition (from 011 . . . 10 to 011 . . . 11 in two’s
complement coding) should occur for an analog voltage 1 1/2 LSB
below the nominal +full scale (+2.499886 V for the 2.5 V range).
The +full-scale error is the deviation of the actual level of the
last transition from the ideal level.
SNR is the ratio of the rms value of the actual input signal to the
rms sum of all other spectral components below the Nyquist
frequency, excluding harmonics and dc. The value for SNR is
expressed in decibels.
SIGNAL-TO-(NOISE + DISTORTION) RATIO (S/[N+D])
S/(N+D) is the ratio of the rms value of the actual input signal
to the rms sum of all other spectral components below the
Nyquist frequency, including harmonics but excluding dc. The
value for S/(N+D) is expressed in decibels.
–FULL-SCALE ERROR
The first transition (from 100 . . . 00 to 100 . . . 01 in two’s
complement coding) should occur for an analog voltage 1 1/2 LSB
above the nominal –full scale (–2.499962 V for the 2.5 V range).
The –full-scale error is the deviation of the actual level of the
last transition from the ideal level.
APERTURE DELAY
Aperture delay is a measure of the acquisition performance and
is measured from the falling edge of the CNVST input to when
the input signal is held for a conversion.
BIPOLAR ZERO ERROR
The bipolar zero error is the difference between the ideal midscale
input voltage (0 V) and the actual voltage producing the midscale
output code.
TRANSIENT RESPONSE
The time required for the AD7675 to achieve its rated accuracy
after a full-scale step function is applied to its input.
SPURIOUS FREE DYNAMIC RANGE (SFDR)
The difference, in decibels (dB), between the rms amplitude of
the input signal and the peak spurious signal.
REV. 0
–7–
AD7675
–Typical Performance Characteristics
1.00
16000
14687
0.75
14000
12000
10000
8000
6000
4000
2000
0000
0.50
0.25
0.00
–0.25
–0.50
–0.75
887
810
0
0
0
0
0
0
0
0
–1.00
0
16384
32768
CODE
49152
65536
7FF8 7FF9 7FFA 7FFB 7FFC 7FFD 7FFE 7FFF 8000 8001 8002
CODE IN HEXA
TPC 4. Histogram of 16,384 Conversions of a DC Input at
the Code Center
TPC 1. Integral Nonlinearity vs. Code
18
16
14
12
10
8
9000
8000
7000
6000
5000
4000
3000
2000
1000
0000
8246
8118
6
4
2
0
0
0
0
0
0
6
14
0
–1.0
–0.8
–0.6
–0.4
–0.2
0.0
7FFB 7FFC 7FFD 7FFE 7FFF 8000 8001 8002 8003 8004
CODE IN HEXA
NEGATIVE INL – LSB
TPC 5. Typical Negative INL Distribution (40 Units)
TPC 2. Histogram of 16,384 Conversions of a DC Input at
the Code Transition
0
18
16
14
12
10
8
fS = 100 kSPS
fIN = 45.01kHz
SNR = 94dB
THD = –110dB
SFDR = 110dB
SINAD = 93.9dB
–20
–40
–60
–80
–100
–120
–140
–160
–180
6
4
2
0
0
10
20
30
40
50
0
0.2
0.4
0.6
0.8
1.0
FREQUENCY – kHz
POSITIVE INL – LSB
TPC 3. Typical Positive INL Distribution (40 Units)
TPC 6. FFT Plot
–8–
REV. 0
AD7675
100
95
90
85
80
16.0
15.5
15.0
14.5
14.0
50
40
30
20
10
0
OVDD = 2.7V @ 85؇C
OVDD = 2.7V @ 25؇C
SNR
OVDD = 5.0V @ 85؇C
SINAD
OVDD = 5.0V @ 25؇C
ENOB
75
70
13.5
13.0
1
10
100
1000
0
50
100
– pF
150
200
FREQUENCY – kHz
C
L
TPC 7. SNR, S/(N+D), and ENOB vs. Frequency
TPC 10. Typical Delay vs. Load Capacitance CL
100k
10k
1k
96
SNR
SINAD
94
AVDD
100
DVDD
10
1
92
90
88
OVDD
0.1
0.01
0.001
–60
–50
–40
–30
–20
–10
0
10
100
1k
SAMPLING RATE – SPS
10k
100k
INPUT LEVEL – dB
TPC 8. SNR and S/(N+D) vs. Input Level
TPC 11. Operating Currents vs. Sample Rate
96
93
90
87
84
–104
–106
–108
–110
–112
250
DVDD
SNR
200
150
100
THD
50
AVDD
OVDD
0
–55
–55
–35
–15
0
25
45
65
85
105
125
–35
–15
5
25
45
65
85
105
TEMPERATURE – ؇C
TEMPERATURE – ؇C
TPC 9. SNR, THD vs. Temperature
TPC 12. Power-Down Operating Currents vs. Temperature
–9–
REV. 0
AD7675
IN+
SWITCHES
CONTROL
MSB
LSB
SW
+
32,768C 16,384C
4C
2C
C
C
BUSY
REF
CONTROL
LOGIC
COMP
OUTPUT
CODE
REFGND
4C
2C
C
C
32,768C 16,384C
MSB
SW
LSB
–
CNVST
IN–
Figure 3. ADC Simplified Schematic
CIRCUIT INFORMATION
connected to the REFGND input. Therefore, the differential
voltage between the output of IN+ and IN– captured at the
end of the acquisition phase is applied to the comparator inputs,
causing the comparator to become unbalanced.
The AD7675 is a fast, low-power, single-supply, precise 16-bit
analog-to-digital converter (ADC). The AD7675 is capable of
converting 100,000 samples per second (100 kSPS) and allows
power saving between conversions. When operating at 100 SPS,
for example, it consumes typically only 15 µW. This feature
makes the AD7675 ideal for battery-powered applications.
By switching each element of the capacitor array between
REFGND or REF, the comparator input varies by binary
weighted voltage steps (VREF/2, VREF/4 . . . VREF/65536). The
control logic toggles these switches, starting with the MSB first,
in order to bring the comparator back into a balanced condition.
After the completion of this process, the control logic generates
the ADC output code and brings BUSY output low.
The AD7675 provides the user with an on-chip track/hold,
successive approximation ADC that does not exhibit any pipe-
line or latency, making it ideal for multiple multiplexed channel
applications.
The AD7675 can be operated from a single 5 V supply and be
interfaced to either 5 V or 3 V digital logic. It is housed in a
48-lead LQFP package that combines space savings and allows
flexible configurations as either serial or parallel interface. The
AD7675 is pin-to-pin compatible with the AD7660.
Transfer Functions
Using the OB/2C digital input, the AD7675 offers two output
codings: straight binary and two’s complement. The ideal trans-
fer characteristic for the AD7675 is shown in Figure 4.
CONVERTER OPERATION
111...111
111...110
111...101
The AD7675 is a successive approximation analog-to-digital
converter based on a charge redistribution DAC. Figure 3 shows
the simplified schematic of the ADC. The capacitive DAC con-
sists of two identical arrays of 16 binary-weighted capacitors that
are connected to the two comparator inputs.
During the acquisition phase, terminals of the array tied to the
comparator’s input is connected to AGND via SW+ and SW–.
All independent switches are connected to the analog inputs.
Thus, the capacitor arrays are used as sampling capacitors and
acquire both analog signals.
000...010
000...001
000...000
–FS
–FS + 1 LSB
+FS – 1 LSB
+FS – 1.5 LSB
–FS + 0.5 LSB
When the acquisition phase is complete and the CNVST input
goes or is low, a conversion phase is initiated. When the con-
version phase begins, SW+ and SW– are opened first. The two
capacitor arrays are then disconnected from the inputs and
ANALOG INPUT
Figure 4. ADC Ideal Transfer Function
–10–
REV. 0
AD7675
DVDD
ANALOG
SUPPLY
(5V)
100⍀
DIGITAL SUPPLY
(3.3V OR 5V)
NOTE 5
+
+
+
100nF
10F
10F
100nF
100nF
10F
ADR421
AVDD
REF
AGND
DGND
OVDD
OGND
DVDD
SERIAL PORT
2.5V REF
NOTE 1
SCLK
1M⍀
100nF
NOTE 3
50⍀
C
+
REF
50k⍀
1F
SDOUT
NOTE 2
REFGND
BUSY
C/P/DSP
50⍀
–
U1
15⍀
CNVST
D
NOTE 4
IN+
+
ANALOG INPUT+
NOTE 7
C
2.7nF
C
AD8021
AD7675
NOTE 5
OB/2C
SER/PAR
DVDD
50⍀
–
U2
+
CLOCK
CS
RD
15⍀
NOTE 4
IN–
ANALOG INPUT–
BYTESWAP
RESET
PD
C
2.7nF
C
AD8021
NOTE 5
NOTES
1. SEEVOLTAGE REFERENCE INPUT SECTION.
2. WITHTHE RECOMMENDEDVOLTAGE REFERENCES, C
IS 47F. SEE CHAPTERVOLTAGE REFERENCE INPUT SECTION
REF
3. OPTIONAL CIRCUITRY FOR HARDWARE GAIN CALIBRATION.
4. THE AD8021 IS RECOMMENDED. SEE DRIVER AMPLIFIER CHOICE SECTION.
5. SEE ANALOG INPUT SECTION.
6. OPTION, SEE POWER SUPPLY SECTION
7. OPTIONAL LOW JITTER CNVST, SEE CONVERSION CONTROL SECTION.
Figure 5. Typical Connection Diagram. ( 2.5 V Range Shown)
TYPICAL CONNECTION DIAGRAM
the input buffer’s (U1) or (U2) supplies are different from
AVDD. In such case, an input buffer with a short-circuit cur-
rent limitation can be used to protect the part.
Figure 5 shows a typical connection diagram for the AD7675.
Different circuitry shown on this diagram are optional and are
discussed below.
This analog input structure is a true differential structure. By
using these differential inputs, signals common to both inputs
are rejected, as shown in Figure 7, which represents the typical
CMRR over frequency.
Analog Inputs
Figure 6 shows a simplified analog input section of the AD7675.
AVDD
85
80
75
70
65
60
55
50
45
40
R+ = 684⍀
IN+
C
S
C
S
IN–
R– = 684⍀
AGND
Figure 6. AD7675 Simplified Analog Input
The diodes shown in Figure 6 provide ESD protection for the
inputs. Care must be taken to ensure that the analog input sig-
nal never exceeds the absolute ratings on these inputs. This will
cause these diodes to become forward-biased and start conducting
current. These diodes can handle a forward-biased current of
120 mA maximum. This condition could eventually occur when
1k
10k
100k
1M
10M
FREQUENCY – Hz
Figure 7. Analog Input CMRR vs. Frequency
REV. 0
–11–
AD7675
During the acquisition phase, for ac signals, the AD7675 behaves
like a one-pole RC filter consisting of the equivalent resistance
R+, R–, and CS. The resistors R+ and R– are typically 684 Ω
and are lumped components made up of some serial resistors
and the on-resistance of the switches. The capacitor CS is typically
60 pF and is mainly the ADC sampling capacitor. This one pole
filter with a typical –3 dB cutoff frequency of 3.9 MHz reduces
undesirable aliasing effect and limits the noise coming from
the inputs.
one-pole, low-pass filter made by R+, R–, and CS. The SNR
degradation due to the amplifier is:
28
SNRLOSS = 20LOG
784 + f–3 dB (N eN )2
π
4
where
–3 dB is the –3 dB input bandwidth of the AD7675 (3.9 MHz)
f
Because the input impedance of the AD7675 is very high, the
AD7675 can be driven directly by a low impedance source
without gain error. That allows users to put, as shown in
Figure 5, an external one-pole RC filter between the output
of the amplifier output and the ADC analog inputs to even
further improve the noise filtering done by the AD7675 analog
input circuit. However, the source impedance has to be kept
low because it affects the ac performances, especially the total
harmonic distortion. The maximum source impedance depends
on the amount of total harmonic distortion (THD) that can be
tolerated. The THD degrades proportionally to the source
impedance.
or the cutoff frequency of the input filter if any is used.
N is the noise factor of the amplifier (1 if in buffer con-
figuration)
e
N is the equivalent input noise voltage of the op amp in
nV/(Hz)1/2
.
For instance, in the case of a driver with an equivalent input
noise of 2 nV/√Hz like the AD8021 and configured as a buffer,
thus with a noise gain of +1, the SNR degrades by only 0.04 dB
with the filter in Figure 5, and 0.07 dB without.
•
The driver needs to have a THD performance suitable to
that of the AD7675.
Single to Differential Driver
For applications using unipolar analog signals, a single-ended to
differential driver will allow for a differential input into the part.
The schematic is shown in Figure 8.
The AD8021 meets these requirements and is usually appropri-
ate for almost all applications. The AD8021 needs an external
compensation capacitor of 10 pF. This capacitor should have
good linearity as an NPO ceramic or mica type.
The AD8022 could also be used where dual version is needed
and gain of 1 is used.
U1
ANALOG INPUT
AD8021
(UNIPOLAR)
C
C
The AD8132 or the AD8138 could also be used to generate a differ-
ential signal from a single-ended signal. When using the AD8138
with the filter in Figure 5, the SNR degrades by only 0.9 dB.
590⍀
IN+
590⍀
AD7675
The AD829 is another alternative where high-frequency (above
100 kHz) performances are not required. In gain of 1, it requires
an 82 pF compensation capacitor.
IN–
U2
590⍀
590⍀
REF
2.5V REF
AD8021
C
C
The AD8610 is also another option where low-bias current is
needed in low-frequency applications.
2.5V REF
Figure 8. Single-Ended to Differential Driver Circuit
The AD8519, OP162, or the OP184 could also be used.
This configuration, when provided an input signal of 0 to VREF
will produce a differential 2.5 V with a common mode at 1.25 V.
,
Voltage Reference Input
The AD7675 uses an external 2.5 V voltage reference.
If the application can tolerate more noise, the AD8138 can be used.
The voltage reference input REF of the AD7675 has a dynamic
input impedance. Therefore, it should be driven by a low-
impedance source with an efficient decoupling between REF
and REFGND inputs. This decoupling depends on the choice
of the voltage reference but usually consists of a 1 µF ceramic
capacitor and a low ESR tantalum capacitor connected to the
REF and REFGND inputs with minimum parasitic induc-
tance. 47 µF is an appropriate value for the tantalum capacitor
when used with one of the recommended reference voltages:
Driver Amplifier Choice
Although the AD7675 is easy to drive, the driver amplifier needs
to meet at least the following requirements:
•
The driver amplifier and the AD7675 analog input circuit
have to be able to settle for a full-scale step of the capaci-
tor array at a 16-bit level (0.0015%). In the amplifier’s data
sheet, the settling at 0.1% or 0.01% is more commonly speci-
fied. It could significantly differ from the settling time at
16-bit level and, therefore, it should be verified prior to the
driver selection. The tiny op amp AD8021 which combines
ultra low noise and a high gain bandwidth meets this settling
time requirement even when used with a high gain up to 13.
•
The low-noise, low temperature drift ADR421 and AD780
voltage references
•
•
The low-power ADR291 voltage reference
The low-cost AD1582 voltage reference
•
The noise generated by the driver amplifier needs to be kept
as low as possible in order to preserve the SNR and transi-
tion noise performance of the AD7675. The noise coming
from the driver is filtered by the AD7675 analog input circuit
For applications using multiple AD7675s, it is more effective to
buffer the reference voltage with a low-noise, very stable op amp
like the AD8031.
–12–
REV. 0
AD7675
100k
10k
1k
Care should also be taken with the reference temperature coeffi-
cient of the voltage reference which directly affects the full-scale
accuracy if this parameter matters. For instance, a 15 ppm/°C
tempco of the reference changes the full scale by 1 LSB/°C.
VREF , as mentioned in the specification table, could be increased
to AVDD – 1.85 V. The benefit here is the increased SNR
obtained as a result of this increase. Since the input range is
defined in terms of VREF, this would essentially increase the
range to make it a 3 V input range with an AVDD above
4.85 V. The theoretical improvement as a result of this increase
in reference is 1.58 dB (20 log [3/2.5]). Due to the theoretical
quantization noise, however, the observed improvement is
approximately 1 dB. The AD780 can be selected with a 3 V
reference voltage.
100
10
1
0.1
10
100
1k
10k
100k
1M
SAMPLING RATE – SPS
Power Supply
The AD7675 uses three sets of power supply pins: an analog
5 V supply AVDD, a digital 5 V core supply DVDD, and a
digital input/output interface supply OVDD. The OVDD supply
allows direct interface with any logic working between 2.7 V and
5.25 V. To reduce the number of supplies needed, the digital
core (DVDD) can be supplied through a simple RC filter from
the analog supply as shown in Figure 5. The AD7675 is inde-
pendent of power supply sequencing and thus free from supply
voltage induced latchup. Additionally, it is very insensitive to
power supply variations over a wide frequency range as shown
in Figure 9.
Figure 10. Power Dissipation vs. Sample Rate
CONVERSION CONTROL
Figure 11 shows the detailed timing diagrams of the conversion
process. The AD7675 is controlled by the signal CNVST which
initiates conversion. Once initiated, it cannot be restarted or
aborted, even by the power-down input PD, until the conver-
sion is complete. The CNVST signal operates independently of
CS and RD signals.
t2
t1
CNVST
75
70
65
60
55
50
45
40
35
BUSY
t4
t3
t6
t5
MODE ACQUIRE
CONVERT
t7
ACQUIRE
t8
CONVERT
Figure 11. Basic Conversion Timing
For true sampling applications, the recommended operation of
the CNVST signal is as follows:
1k
10k
100k
1M
10M
CNVST must be held high from the previous falling edge of
BUSY, and during a minimum delay corresponding to the
acquisition time t8; then, when CNVST is brought low, a
conversion is initiated and BUSY signal goes high until the
completion of the conversion. Although CNVST is a digital
signal, it should be designed with this special care with fast,
clean edges and levels, with minimum overshoot and under-
shoot or ringing.
FREQUENCY – Hz
Figure 9. PSRR vs. Frequency
POWER DISSIPATION
The AD7675 automatically reduces its power consumption at
the end of each conversion phase. During the acquisition phase,
the operating currents are very low which allows a significant
power saving when the conversion rate is reduced as shown in
Figure 10. This feature makes the AD7675 ideal for very low-
power battery applications.
For applications where the SNR is critical, the CNVST signal should
have a very low jitter. Some solutions to achieve that are to use a
dedicated oscillator for CNVST generation or, at least, to clock
it with a high-frequency low-jitter clock, as shown in Figure 5.
It should be noted that the digital interface remains active even
during the acquisition phase. To reduce the operating digital
supply currents even further, the digital inputs need to be driven
close to the power rails (i.e., DVDD and DGND) and OVDD
should not exceed DVDD by more than 0.3 V.
REV. 0
–13–
AD7675
RESET
PARALLEL INTERFACE
t9
The AD7675 is configured to use the parallel interface (Figure 13)
when the SER/PAR is held low. The data can be read either
after each conversion, which is during the next acquisition
phase, or during the following conversion as shown, respectively,
in Figure 14 and Figure 15. When the data is read during the
conversion, however, it is recommended that it be read-only
during the first half of the conversion phase. That avoids any
potential feedthrough between voltage transients on the digital
interface and the most critical analog conversion circuitry.
BUSY
DATA
t8
CS
CNVST
RD
Figure 12. RESET Timing
For other applications, conversions can be automatically initi-
ated. If CNVST is held low when BUSY is low, the AD7675
controls the acquisition phase and then automatically initiates a
new conversion. By keeping CNVST low, the AD7675 keeps
the conversion process running by itself. It should be noted that
the analog input has to be settled when BUSY goes low. Also, at
power-up, CNVST should be brought low once to initiate the
conversion process. In this mode, the AD7675 could sometimes
run slightly faster than the guaranteed limit of 100 kSPS.
BUSY
DATA
BUS
CURRENT
CONVERSION
t12
t13
Figure 14. Slave Parallel Data Timing for Reading
(Read after Convert)
CS = 0
t1
CNVST,
RD
DIGITAL INTERFACE
The AD7675 has a versatile digital interface; it can be interfaced
with the host system by using either a serial or parallel interface.
The serial interface is multiplexed on the parallel data bus. The
AD7675 digital interface also accommodates both 3 V or 5 V
logic by simply connecting the OVDD supply pin of the AD7675
to the host system interface digital supply. Finally, by using the
OB/2C input pin, either two’s complement or straight binary
coding can be used.
BUSY
t4
t3
PREVIOUS
DATA
BUS
CONVERSION
t12
t13
Figure 15. Slave Parallel Data Timing for Reading (Read
During Convert)
The two signals CS and RD control the interface. When at least
one of these signals is high, the interface outputs are in high
impedance. Usually, CS allows the selection of each AD7675 in
multicircuits applications and is held low in a single AD7675
design. RD is generally used to enable the conversion result on
the data bus.
The BYTESWAP pin allows a glueless interface to an 8-bit bus.
As shown in Figure 16, the LSB byte is output on D[7:0] and
the MSB is output on D[15:8] when BYTESWAP is low. When
BYTESWAP is high, the LSB and MSB bytes are swapped and
the LSB is output on D[15:8] and the MSB is output on D[7:0].
By connecting BYTESWAP to an address line, the 16-bit data
can be read in two bytes on either D[15:8] or D[7:0].
CS = RD = 0
t1
CNVST
t10
CS
RD
t4
BUSY
t3
t11
DATA
BUS
PREVIOUS CONVERSION DATA
NEW DATA
BYTE
Figure 13. Master Parallel Data Timing for Reading
(Continuous Read)
HI-Z
HI-Z
HI-Z
HIGH BYTE
LOW BYTE
PINS D[15:8]
PINS D[7:0]
t12
t12
t13
HI-Z
LOW BYTE
HIGH BYTE
Figure 16. 8-Bit Parallel Interface
–14–
REV. 0
AD7675
SERIAL INTERFACE
serial data is valid. The serial clock SCLK and the SYNC signal
can be inverted if desired. The output data is valid on both the
rising and falling edge of the data clock. Depending on RDC/
SDIN input, the data can be read after each conversion, or
during the following conversion. Figure 17 and Figure 18 show
the detailed timing diagrams of these two modes.
The AD7675 is configured to use the serial interface when the
SER/PAR is held high. The AD7675 outputs 16 bits of data,
MSB first, on the SDOUT pin. This data is synchronized with
the 16 clock pulses provided on the SCLK pin.
MASTER SERIAL INTERFACE
Internal Clock
The AD7675 is configured to generate and provide the serial
data clock SCLK when the EXT/INT pin is held low. The AD7675
also generates a SYNC signal to indicate to the host when the
Usually, because the AD7675 has a longer acquisition phase
than the conversion phase, the data is read immediately after
conversion. That makes the mode master, read after conversion,
the most recommended serial mode when it can be used.
RDC/SDIN = 0
INVSCLK = INVSYNC = 0
EXT/INT = 0
CS, RD
t3
CNVST
t28
BUSY
t30
t29
t25
SYNC
t14
t18
t19
t24
t20
t21
2
t26
1
3
14
15
16
SCLK
t15
t27
X
D15
D14
t23
D2
D1
D0
SDOUT
t16
t22
Figure 17. Master Serial Data Timing for Reading (Read after Convert)
RDC/SDIN = 1
INVSCLK = INVSYNC = 0
EXT/INT = 0
CS, RD
t1
CNVST
t3
BUSY
t17
t25
SYNC
t14
t19
t20 t21
t24
t26
t15
SCLK
1
2
3
14
15
16
t18
t27
X
D15
D14
t23
D2
D1
D0
SDOUT
t16
t22
Figure 18. Master Serial Data Timing for Reading (Read Previous Conversion during Convert)
REV. 0
–15–
AD7675
In read-after-conversion mode, it should be noted that, unlike in
other modes, the signal BUSY returns low after the 16 data bits
are pulsed out and not at the end of the conversion phase which
results in a longer BUSY width.
the conversion phase. For this reason, it is recommended that when
an external clock is being provided, it is a discontinuous clock
that is toggling only when BUSY is low or, more importantly,
that it does not transition during the latter half of BUSY high.
In read-during-conversion mode, the serial clock and data toggle
at appropriate instances which minimizes potential feedthrough
between digital activity and the critical conversion decisions.
External Discontinuous Clock Data Read after Conversion
This mode is the most recommended of the serial slave modes.
Figure 19 shows the detailed timing diagrams of this method.
After a conversion is complete, indicated by BUSY returning
low, the result of this conversion can be read while both CS and
RD are low. The data is shifted out, MSB first, with 16 clock
pulses and is valid on both the rising and falling edge of the clock.
To accommodate slow digital hosts, the serial clock can be
slowed down by using DIVSCLK.
SLAVE SERIAL INTERFACE
External Clock
One of the advantages of this method is that the conversion
performance is not degraded because there is no voltage transient
on the digital interface during the conversion process.
The AD7675 is configured to accept an externally supplied
serial data clock on the SCLK pin when the EXT/INT pin is
held high. In this mode, several methods can be used to read the
data. The external serial clock is gated by CS and the data are
output when both CS and RD are low. Thus, depending on
CS, the data can be read after each conversion or during the
following conversion. The external clock can be either a con-
tinuous or discontinuous clock. A discontinuous clock can be
either normally high or normally low when inactive. Figure 19
and Figure 20 show the detailed timing diagrams of these meth-
ods. Usually, because the AD7675 has a longer acquisition
phase than the conversion phase, the data are read immediately
after conversion.
Another advantage is the ability to read the data at any speed up
to 40 MHz, which accommodates both slow digital host inter-
face and the fastest serial reading.
Finally, in this mode only, the AD7675 provides a “daisy chain”
feature using the RDC/SDIN input pin for cascading multiple
converters together. This feature is useful for reducing compo-
nent count and wiring connections when it is desired as it is, for
instance, in isolated multiconverters applications.
An example of the concatenation of two devices is shown in
Figure 21. Simultaneous sampling is possible by using a com-
mon CNVST signal. It should be noted that the RDC/SDIN
input is latched on the opposite edge of SCLK of the one used
to shift out the data on SDOUT. Hence, the MSB of the
“upstream” converter just follows the LSB of the “downstream”
converter on the next SCLK cycle.
While the AD7675 is performing a bit decision, it is important
that voltage transients not occur on digital input/output pins or
degradation of the conversion result could occur. This is particu-
larly important during the second half of the conversion phase
because the AD7675 provides error-correction circuitry that can
correct for an improper bit decision made during the first half of
INVSCLK = 0
EXT/INT = 1
RD = 0
CS
BUSY
t35
t36
1
t37
SCLK
2
3
14
15
16
17
18
t31
t32
SDOUT
X
D15
D14
D13
X13
D1
X1
D0
X15
Y15
X14
Y14
t16
t34
SDIN
X15
X14
X0
t33
Figure 19. Slave Serial Data Timing for Reading (Read after Convert)
–16–
REV. 0
AD7675
External Clock Data Read During Conversion
16-bit wide interface or with a general purpose serial port or I/O
ports on a microcontroller. A variety of external buffers can be
used with the AD7675 to prevent digital noise from coupling
into the ADC. The following sections illustrate the use of the
AD7675 with an SPI-equipped microcontroller, and the
ADSP-21065L and ADSP-218x signal processors.
Figure 20 shows the detailed timing diagrams of this method.
During a conversion, while both CS and RD are low, the result
of the previous conversion can be read. The data is shifted out,
MSB first, with 16 clock pulses, and is valid on both rising and
falling edges of the clock. The 16 bits have to be read before the
current conversion is complete. If that is not done, RDERROR is
pulsed high and can be used to interrupt the host interface to
prevent incomplete data reading. There is no “daisy chain”
feature in this mode, and RDC/SDIN input should always be
tied either high or low.
SPI Interface (MC68HC11)
Figure 22 shows an interface diagram between the AD7675 and
an SPI-equipped microcontroller like the MC68HC11. To
accommodate the slower speed of the microcontroller, the
AD7675 acts as a slave device and data must be read after con-
version. This mode also allows the “daisy chain” feature. The
convert command could be initiated in response to an internal
timer interrupt. The reading of output data, one byte at a time if
necessary, could be initiated in response to the end-of-conversion
signal (BUSY going low) using an interrupt line of the micro-
controller. The Serial Peripheral Interface (SPI) on the MC68HC11
is configured for master mode (MSTR) = 1, Clock Polarity Bit
(CPOL) = 0, Clock Phase Bit (CPHA) = 1 and SPI interrupt
enable (SPIE) = 1 by writing to the SPI Control Register (SPCR).
The IRQ is configured for edge-sensitive-only operation
(IRQE = 1 in OPTION register).
To reduce performance degradation due to digital activity, a fast
discontinuous clock of 18 MHz at least is recommended to ensure
that all the bits are read during the first half of the conversion
phase. For this reason, this mode is more difficult to use.
MICROPROCESSOR INTERFACING
The AD7675 is ideally suited for traditional dc measurement
applications supporting a microprocessor, and ac signal process-
ing applications interfacing to a digital signal processor. The
AD7675 is designed to interface either with a parallel 8-bit or
INVSCLK = 0
EXT/INT = 1
RD = 0
CS
CNVST
BUSY
t3
t35
t36 t37
SCLK
1
2
3
14
15
16
t31
t32
SDOUT
X
D15
D14
D13
D1
D0
t16
Figure 20. Slave Serial Data Timing for Reading (Read Previous Conversion during Convert)
BUSY
OUT
BUSY
BUSY
AD7675 #2
(UPSTREAM)
AD7675 #1
(DOWNSTREAM)
DATA
OUT
RDC/SDIN
SDOUT
RDC/SDIN
SDOUT
CNVST
CS
CNVST
CS
SCLK
SCLK
SCLK IN
CS IN
CNVST IN
Figure 21. Two AD7675s in a “Daisy Chain” Configuration
REV. 0
–17–
AD7675
DVDD
ground planes should be joined in only one place, preferably
underneath the AD7675, or, at least, as close as possible to the
AD7675. If the AD7675 is in a system where multiple devices
require analog to digital ground connections, the connection
should still be made at one point only, a star ground point,
which should be established as close as possible to the AD7675.
MC68HC11*
AD7675*
SER/PAR
EXT/INT
CS
BUSY
SDOUT
SCLK
IRQ
RD
MISO/SDI
SCK
It is recommended that running digital lines under the device
should be avoided as these will couple noise onto the die. The
analog ground plane should be allowed to run under the AD7675
to avoid noise coupling. Fast switching signals like CNVST or
clocks should be shielded with digital ground to avoid radiating
noise to other sections of the board, and should never run near
analog signal paths. Crossover of digital and analog signals
should be avoided. Traces on different but close layers of the
board should run at right angles to each other. This will reduce the
effect of feedthrough through the board.
INVSCLK
CNVST
I/O PORT
*ADDITIONAL PINS OMITTED FOR CLARITY
Figure 22. Interfacing the AD7675 to SPI Interface
ADSP-21065L in Master Serial Interface
As shown in Figure 23, the AD7675 can be interfaced to the
ADSP-21065L using the serial interface in master mode without any
glue logic required. This mode combines the advantages of reducing
the wire connections and the ability to read the data during or after
conversion maximum speed transfer (DIVSCLK[0:1] both low).
The power supply lines to the AD7675 should use as large a
trace as possible to provide low impedance paths and reduce the
effect of glitches on the power supply lines. Good decoupling is
also important to lower the supplies impedance presented to
the AD7675 and reduce the magnitude of the supply spikes.
Decoupling ceramic capacitors, typically 100 nF, should be
placed on each power supplies pins AVDD, DVDD, and OVDD
close to, and ideally right up against these pins and their corre-
sponding ground pins. Additionally, low ESR 10 µF capacitors
should be located in the vicinity of the ADC to further reduce
low-frequency ripple.
The AD7675 is configured for the internal clock mode (EXT/
INT low) and acts, therefore, as the master device. The convert
command can be generated by either an external low jitter oscil-
lator or, as shown, by a FLAG output of the ADSP-21065L or
by a frame output TFS of one serial port of the ADSP-21065L
which can be used like a timer. The serial port on the ADSP-
21065L is configured for external clock (IRFS = 0), rising edge
active (CKRE = 1), external late framed sync signals (IRFS = 0,
LAFS = 1, RFSR = 1) and active high (LRFS = 0). The serial
port of the ADSP-21065L is configured by writing to its receive
control register (SRCTL)—see ADSP-2106x SHARC User’s
Manual. Because the serial port within the ADSP-21065L will
be seeing a discontinuous clock, an initial word reading has to
be done after the ADSP-21065L has been reset to ensure that
the serial port is properly synchronized to this clock during each
following data read operation.
The DVDD supply of the AD7675 can be either a separate
supply or come from the analog supply, AVDD, or from the
digital interface supply, OVDD. When the system digital supply
is noisy, or fast switching digital signals are present, it is recom-
mended if no separate supply is available, to connect the DVDD
digital supply to the analog supply AVDD through an RC filter
as shown in Figure 5, and connect the system supply to the inter-
face digital supply OVDD and the remaining digital circuitry.
When DVDD is powered from the system supply, it is useful to
insert a bead to further reduce high-frequency spikes.
DVDD
ADSP-21065L*
AD7675*
SHARC
SER/PAR
The AD7675 has four different ground pins: REFGND, AGND,
DGND, and OGND. REFGND senses the reference voltage and
should be a low-impedance return to the reference because it
carries pulsed currents. AGND is the ground to which most
internal ADC analog signals are referenced. This ground must
be connected with the least resistance to the analog ground
plane. DGND must be tied to the analog or digital ground plane
depending on the configuration. OGND is connected to the
digital system ground.
RDC/SDIN
RD
SYNC
SDOUT
SCLK
RFS
EXT/INT
DR
CS
RCLK
INVSYNC
INVSCLK
CNVST
FLAG OR TFS
*ADDITIONAL PINS OMITTED FOR CLARITY
Figure 23. Interfacing to the ADSP-21065L Using
the Serial Master Mode
The layout of the decoupling of the reference voltage is important.
The decoupling capacitor should be close to the ADC and connected
with short and large traces to minimize parasitic inductances.
APPLICATION HINTS
Evaluating the AD7675 Performance
Layout
A recommended layout for the AD7675 is outlined in the evalu-
ation board for the AD7675. The evaluation board package
includes a fully assembled and tested evaluation board, docu-
mentation, and software for controlling the board from a PC
via the Eval-Control BRD2.
The AD7675 has very good immunity to noise on the power
supplies as can be seen in Figure 21. However, care should still
be taken with regard to grounding layout.
The printed circuit board that houses the AD7675 should be
designed so the analog and digital sections are separated and
confined to certain areas of the board. This facilitates the use of
ground planes that can be easily separated. Digital and analog
–18–
REV. 0
AD7675
OUTLINE DIMENSIONS
Dimensions shown in inches and (mm).
48-Lead Quad Flatpack (LQFP)
(ST-48)
0.063 (1.60)
MAX
0.354 (9.00) BSC SQ
0.030 (0.75)
0.018 (0.45)
37
48
36
1
0.276
(7.00)
BSC
SQ
TOP VIEW
(PINS DOWN)
COPLANARITY
0.003 (0.08)
12
25
0؇
MIN
13
24
0.011 (0.27)
0.006 (0.17)
0.019 (0.5)
BSC
0.008 (0.2)
0.004 (0.09)
0.057 (1.45)
0.053 (1.35)
7؇
0؇
0.006 (0.15)
0.002 (0.05)
SEATING
PLANE
REV. 0
–19–
–20–
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