AD8124ACPZ-R7 [ADI]
Triple Differential Receiver with 200 Meter Adjustable Cable Equalization;
| 型号： | AD8124ACPZ-R7 |
| 厂家： | 
ADI |
| 描述： | Triple Differential Receiver with 200 Meter Adjustable Cable Equalization 商用集成电路 |
| 文件： | 总16页 (文件大小：929K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
Triple Differential Receiver with
200 Meter Adjustable Cable Equalization
Data Sheet
AD8124
FEATURES
FUNCTIONAL BLOCK DIAGRAM
V
V
V
V
PEAK
POLE
OFFSET GAIN
Compensates cables to 200 meters for wideband video
All resolutions through UXGA
Fast rise and fall times
AD8124
8 ns with 2 V step at 200 meters of UTP cable
37 dB peak gain at 100 MHz
Two frequency response gain adjustment pins
–IN
+IN
R
OUT
OUT
OUT
R
G
B
R
–IN
High frequency peaking adjustment (VPEAK
Broadband flat gain adjustment (VGAIN
Pole location adjustment pin (VPOLE
)
G
G
)
+IN
)
–
IN
B
Compensates for variations between cables
+IN
Can be optimized for either UTP or coaxial cable
B
DC output offset adjust (VOFFSET
Low output offset voltage: 24 mV
Compensates both RGB and YPbPr
Two on-chip comparators with hysteresis
Can be used for common-mode sync extraction
Available in 40-lead, 6 mm × 6 mm LFCSP
)
–IN
+IN
–IN
+IN
CMP1
CMP1
CMP2
CMP2
OUT
OUT
CMP1
CMP2
Figure 1.
APPLICATIONS
Keyboard-video-mouse (KVM)
Digital signage
RGB video over UTP cables
Professional video projection and distribution
HD video
Security video
GENERAL DESCRIPTION
The AD8124 is a triple, high speed, differential receiver and
equalizer that compensates for the transmission losses of UTP
and coaxial cables up to 200 meters in length. Various gain stages
are summed together to best approximate the inverse frequency
response of the cable. Logic circuitry inside the AD8124 controls
the gain functions of the individual stages so that the lowest
noise can be achieved at short-to-medium cable lengths. This
technique optimizes its performance for low noise, short-to-
medium range applications, while at the same time provides
the high gain bandwidth required for longer cable equalization
(up to 200 meters). Each channel features a high impedance
differential input that is ideal for interfacing directly with the cable.
The AD8124 has three control pins for optimal cable
compensation, as well as an output offset adjust pin. Two
voltage-controlled pins are used to compensate for different
cable lengths; the VPEAK pin controls the amount of high frequency
peaking and the VGAIN pin adjusts the broadband flat gain, which
compensates for the low frequency flat cable loss.
For added flexibility, an optional pole adjustment pin, VPOLE
allows movement of the pole locations, allowing for the
compensation of different gauges and types of cable as well
,
as variations between different cables and/or equalizers. The
OFFSET pin allows the dc voltage at the output to be adjusted,
V
adding flexibility for dc-coupled systems.
The AD8124 is available in a 6 mm × 6 mm, 40-lead LFCSP
and is rated to operate over the extended temperature range of
−40°C to +85°C.
Rev. A
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• AD8124: Triple Differential Receiver with 200 Meter
Adjustable Cable Equalization Data Sheet
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AD8124
Data Sheet
TABLE OF CONTENTS
Features .............................................................................................. 1
Applications Information .............................................................. 11
Basic Operation .......................................................................... 11
Comparators ............................................................................... 11
Sync Pulse Extraction Using Comparators............................. 12
Using the VPEAK, VPOLE, VGAIN, and VOFFSET Inputs................... 12
Using the AD8124 with Coaxial Cable.................................... 13
Driving 75 Ω Video Cable with the AD8124.......................... 13
Driving a Capacitive Load......................................................... 13
Power Supply Filtering............................................................... 13
Layout and Power Supply Decoupling Considerations......... 14
Power-Down ............................................................................... 14
Outline Dimensions....................................................................... 15
Ordering Guide .......................................................................... 15
Applications....................................................................................... 1
Functional Block Diagram .............................................................. 1
General Description......................................................................... 1
Revision History ............................................................................... 2
Specifications..................................................................................... 3
Absolute Maximum Ratings............................................................ 5
Thermal Resistance ...................................................................... 5
Maximum Power Dissipation ..................................................... 5
ESD Caution.................................................................................. 5
Pin Configuration and Function Description .............................. 6
Typical Performance Characteristics ............................................. 7
Theory of Operation ...................................................................... 10
Input Common-Mode Voltage Range Considerations ......... 10
REVISION HISTORY
12/15—Rev. 0 to Rev. A
Changes to Figure 3.......................................................................... 6
Updated Outline Dimensions....................................................... 15
Changes to Ordering Guide .......................................................... 15
1/11—Revision 0: Initial Version
Rev. A | Page 2 of 15
Data Sheet
AD8124
SPECIFICATIONS
TA = 25°C, VS = 5 V, RL = 150 Ω, Belden Cable (BL-7987R), VOFFSET = 0 V, V PEAK, VGAIN, and VPOLE are set to recommended settings shown in
Figure 16, unless otherwise noted.
Table 1.
Parameter
Test Conditions/Comments
Min Typ
Max Unit
DYNAMIC PERFORMANCE
10% to 90% Rise/Fall Time
Settling Time to 2%
VOUT = 2 V step, 200 meters Cat-5
VOUT = 2 V step, 200 meters Cat-5
VOUT = 2 V p-p, <10 meters Cat-5
VOUT = 2 V p-p, 200 meters Cat-5
200 meter setting, integrated to 160 MHz
8
ns
ns
MHz
MHz
mV rms
47
110
52
4
–3 dB Large Signal Bandwidth
Integrated Output Voltage Noise
INPUT DC PERFORMANCE
Input Voltage Range
Maximum Differential Voltage Swing
Voltage Gain
−IN and +IN
3.0
4
1
V
V p-p
V/V
dB
dB
dB
MΩ
MΩ
pF
ΔVO/ΔVI, VGAIN set for 0 meters of cable
At dc, VPEAK = VGAIN = VPOLE = 0 V
At dc, VPEAK = 1.15 V, VGAIN = 1.4 V, VPOLE = 1.5 V
At 1 MHz, VPEAK = 1.15 V, VGAIN = 1.4 V, VPOLE = 1.5 V
Common mode
Differential
Common mode
Differential
Common-Mode Rejection Ratio (CMRR)
−86
−65
−50
4.4
3.7
1.0
0.5
2.4
30
Input Resistance
Input Capacitance
pF
Input Bias Current
VOFFSET Pin Current
VGAIN Pin Current
VPEAK Pin Current
VPOLE Pin Current
µA
µA
µA
µA
µA
0.5
0.4
0.4
ADJUSTMENT PINS
VPEAK Input Voltage Range
VPOLE Input Voltage Range
VGAIN Input Voltage Range
VOFFSET to OUT Gain
Maximum Flat Gain
OUTPUT CHARACTERISTICS
Output Voltage Swing
Relative to GND
Relative to GND
Relative to GND
OUT/VOFFSET, range limited by output swing
VGAIN = 1.5 V
0 to 1.5
V
V
V
V/V
dB
0 to 1.5
0 to 1.5
1
1.9
150 Ω load
−3.75 to +3.69
V
1 kΩ load
−3.66 to +3.69
V
Output Offset Voltage
Referred to output, VPEAK = VGAIN = VPOLE = 0 V
Referred to output, VPEAK = 1.15 V, VGAIN = 1.4 V,
24
37
mV
mV
V
POLE = 1.5 V
Output Offset Voltage Drift
POWER SUPPLY
Referred to output
33
µV/°C
Operating Voltage Range
4.5
5.5
V
Positive Quiescent Supply Current
Negative Quiescent Supply Current
Supply Current Drift, ICC/IEE
Positive Power Supply Rejection Ratio
Negative Power Supply Rejection Ratio
Power Down, VIH (Minimum)
Power Down, VIL (Maximum)
Positive Supply Current, Powered Down
Negative Supply Current, Powered Down
132
126
80
−51
−63
1.1
0.8
1.1
0.7
mA
mA
µA/°C
dB
dB
V
V
µA
µA
DC, referred to output
DC, referred to output
Minimum Logic 1 voltage
Maximum Logic 0 voltage
VPEAK = VGAIN = VPOLE = 0 V
VPEAK = VGAIN = VPOLE = 0 V
Rev. A | Page 3 of 15
AD8124
Data Sheet
Parameter
Test Conditions/Comments
Min Typ
3.33/0.043
Max Unit
COMPARATORS
Output Voltage Levels
Hysteresis
Propagation Delay
Rise/Fall Times
Output Resistance
OPERATING TEMPERATURE RANGE
VOH/VOL
VHYST
tPD, LH/tPD, HL
tRISE/tFALL
V
70
mV
ns
ns
Ω
17.5/10.0
9.3/9.3
0.03
−40
+85
°C
Rev. A | Page 4 of 15
Data Sheet
AD8124
ABSOLUTE MAXIMUM RATINGS
Table 2.
voltage difference between the associated power supply and the
output voltage. The total power dissipation due to load currents
is then obtained by taking the sum of the individual power
dissipations. RMS output voltages must be used when dealing
with ac signals.
Parameter
Rating
Supply Voltage
11 V
Power Dissipation
See Figure 2
VS− − 0.3 V to VS+ + 0.3 V
−65°C to +125°C
−40°C to +85°C
300°C
Input Voltage (Any Input)
Storage Temperature Range
Operating Temperature Range
Lead Temperature (Soldering, 10 sec)
Junction Temperature
Airflow reduces θJA. In addition, more metal directly in contact
with the package leads from metal traces, through holes, ground,
and power planes reduces the θJA. The exposed paddle on the
underside of the package must be soldered to a pad on the PCB
surface that is thermally connected to a solid plane (usually the
ground plane) to achieve the specified θJA.
150°C
Stresses at or above those listed under Absolute Maximum
Ratings may cause permanent damage to the product. This is a
stress rating only; functional operation of the product at these
or any other conditions above those indicated in the operational
section of this specification is not implied. Operation beyond
the maximum operating conditions for extended periods may
affect product reliability.
Figure 2 shows the maximum safe power dissipation in the
package vs. the ambient temperature for the 40-lead LFCSP
(29°C/W) on a JEDEC standard 4-layer board with the underside
paddle soldered to a pad that is thermally connected to a PCB
plane. θJA values are approximations.
7
THERMAL RESISTANCE
6
5
4
3
2
1
0
θJA is specified for the worst-case conditions; that is, θJA is
specified for the device soldered in a circuit board in still air.
Table 3. Thermal Resistance with the Underside Pad
Connected to the Plane
Package Type/PCB Type
θJA
Unit
40-Lead LFCSP/4-Layer
29
°C/W
MAXIMUM POWER DISSIPATION
The maximum safe power dissipation in the AD8124 package
is limited by the associated rise in junction temperature (TJ) on
the die. At approximately 150°C, which is the glass transition
temperature, the plastic changes its properties. Even temporarily
exceeding this temperature limit can change the stresses that the
package exerts on the die, permanently shifting the parametric
performance of the AD8124. Exceeding a junction temperature
of 175°C for an extended time can result in changes in the
silicon devices, potentially causing failure.
–40
–20
0
20
40
60
80
AMBIENT TEMPERATURE (°C)
Figure 2. Maximum Power Dissipation vs. Temperature for a 4-Layer Board
ESD CAUTION
The power dissipated in the package (PD) is the sum of the
quiescent power dissipation and the power dissipated in the
package due to the load drive for all outputs. The quiescent
power is the voltage between the supply pins (VS) times the
quiescent current (IS). The power dissipation due to each load
current is calculated by multiplying the load current by the
Rev. A | Page 5 of 15
AD8124
Data Sheet
PIN CONFIGURATION AND FUNCTION DESCRIPTION
AD8124
TOP VIEW
(Not to Scale)
NIC
1
2
NIC
30
V
+IN
–IN
29 S+
28 PD
V
CMP1
CMP1
CMP1
1
2
3
OUT
4
27
26
25
24
23
22
POLE
PEAK
GAIN
V
_CMP
V
V
5
S+
OUT
–IN
6
CMP2
CMP2
CMP2
_CMP
NIC
7
GND
8
9
10
V
+IN
OFFSET
S–
21 NIC
V
V
S–
NIC = NO INTERNAL CONNECT
NOTES
1. EXPOSED PADDLE ON THE BOTTOM OF THE PACKAGE
MUST BE CONNECTED TO A PCB PLANE TO ACHIEVE
SPECIFIED THERMAL RESISTANCE.
Figure 3. Pin Configuration
Table 4. Pin Function Descriptions
Pin No.
Mnemonic
Description
1, 10, 20, 21, 30, 40
NIC
No Internal Connection.
2
3
4
5
6
7
8
9
+INCMP1
−INCMP1
OUTCMP1
VS+_CMP
OUTCMP2
−INCMP2
+INCMP2
VS−_CMP
VS−
OUTB
VS+
OUTG
OUTR
VOFFSET
GND
Positive Input, Comparator 1.
Negative Input, Comparator 1.
Output, Comparator 1.
Positive Power Supply, Comparator. Must be connected to VS+.
Output, Comparator 2.
Negative Input, Comparator 2.
Positive Input, Comparator 2.
Negative Power Supply, Comparator. Must be connected to VS−.
Negative Power Supply, Equalizer Sections.
Output, Blue Channel.
Positive Power Supply, Equalizer Sections.
Output, Green Channel.
Output, Red Channel.
Output Offset Control Voltage.
Signal Ground Reference.
11, 14, 17, 22, 33
12
13, 16, 19, 29, 36
15
18
23
24, 39
25
26
27
28
VGAIN
VPEAK
VPOLE
PD
Broadband Flat Gain Control Voltage.
Equalizer High Frequency Boost Control Voltage.
Equalizer Pole Location Adjustment Control Voltage.
Power Down.
31
+INR
Positive Input, Red Channel.
32
34
35
37
−INR
+ING
−ING
+INB
Negative Input, Red Channel.
Positive Input, Green Channel.
Negative Input, Green Channel.
Positive Input, Blue Channel.
38
−INB
Negative Input, Blue Channel.
Exposed Underside Pad
Thermal Plane Connection. Connect to any PCB plane with voltage between VS+ and VS−.
Rev. A | Page 6 of 15
Data Sheet
AD8124
TYPICAL PERFORMANCE CHARACTERISTICS
TA = 25°C, VS = 5 V, RL = 150 Ω, Belden Cable (BL-7987R), VOFFSET = 0 V, V PEAK, VGAIN, and VPOLE are set to recommended settings shown in
Figure 16, unless otherwise noted.
4
3
V
V
V
= 0V
= 0V
= 1V p-p
V
= 2V p-p
PEAK
POLE
O
3
O
2
0
1
0
–3
–6
–9
–12
–1
–2
–3
–4
–5
–6
50m
V
V
V
= 0V
= 0.6V
= 1.5V
100m
150m
200m
GAIN
GAIN
GAIN
100k
1M
10M
100M
1G
100k
1M
10M
100M
FREQUENCY (Hz)
FREQUENCY (Hz)
Figure 4. Frequency Response for Various VGAIN Without Cable
Figure 7. Equalized Frequency Response for Various Cable Lengths
40
120
V
V
V
= 0.6V
= 1.5V
= 1V p-p
V
= 2V p-p
GAIN
POLE
OUT
30
20
O
100
80
60
40
20
10
0
–10
–20
–30
–40
–50
–60
V
V
= 0V
= 1.5V
PEAK
PEAK
100k
1M
10M
100M
0
25
50
75
100
125
150
175
200
FREQUENCY (Hz)
CABLE LENGTH (meters)
Figure 5. Frequency Response for Various VPEAK Without Cable
Figure 8. Equalized −3 dB Bandwidth vs. Cable Length
40
6
4
V
V
V
= 0.6V
= 0V
= 0V
V
V
V
= 0.6V
= 1.5V
= 1V p-p
GAIN
PEAK
POLE
GAIN
PEAK
30
20
O
10
2
0
–10
–20
–30
–40
–50
–60
0
–2
–4
–6
V
V
= 0V
= 1.5V
POLE
POLE
INPUT
OUTPUT
100k
1M
10M
100M
0
50
100 150 200 250 300 350 400 450 500
TIME (ns)
FREQUENCY (Hz)
Figure 6. Frequency Response for Various VPOLE Without Cable
Figure 9. Overdrive Recovery
Rev. A | Page 7 of 15
AD8124
Data Sheet
1.5
1.0
0.5
0
1.5
1.0
50m
200m
50m
200m
0.5
0
–0.5
–1.0
–0.5
–1.0
–1.5
–1.5
0
50
100 150 200 250 300 350 400 450 500
TIME (ns)
0
2
4
6
8
10
TIME (µs)
Figure 10. Pulse Response for Various Cable Lengths (2 MHz)
Figure 13. Pulse Response for Various Cable Lengths (100 kHz)
1000
6
5
4
3
2
1
100
0m
200m
0
100k
0
25
1M
10M
100M
50
75
100
125
150
175
200
FREQUENCY (Hz)
CABLE LENGTH (meters)
Figure 11. Output Voltage Noise vs. Frequency for Various Cable Lengths
Figure 14. Integrated Output Voltage Noise vs. Cable Lengths
20
20
V
V
= 0V, V
PEAK
= 0V, V
= 1.15V, V
= 0V
= 1.5V
POLE
V
V
= 0V, V
= 1.4V, V
= 0V, V
= 0V
= 1.5V
POLE
GAIN
GAIN
POLE
GAIN
GAIN
PEAK
POLE
= 1.4V, V
= 1.15V, V
10
0
PEAK
PEAK
10
0
–10
–20
–30
–40
–50
–60
–70
–80
–10
–20
–30
–40
–50
–60
–70
–80
0.1
1
10
100
100k
1M
10M
100M
FREQUENCY (Hz)
FREQUENCY (MHz)
Figure 15. Crosstalk vs. Frequency
Figure 12. CMRR vs. Frequency
Rev. A | Page 8 of 15
Data Sheet
AD8124
2.0
1.8
1.6
1.4
1.2
1.0
0.8
0.6
0.4
0.2
0
2.0
V
V
V
V
V
V
PEAK
POLE
GAIN
PEAK
POLE
GAIN
1.8
1.6
1.4
1.2
1.0
0.8
0.6
0.4
0.2
0
25
50
75
100
125
150
175
200
0
25
50
75
100
125
150
175
200
CABLE LENGTH (meters)
CABLE LENGTH (meters)
Figure 16. Recommended Settings for UTP Cable
Figure 17. Recommended Settings for Coaxial Cable
Rev. A | Page 9 of 15
AD8124
Data Sheet
THEORY OF OPERATION
The AD8124 is a unity-gain, triple, wideband, low noise analog
line equalizer that compensates for losses in UTP and coaxial
cables up to 200 meters in length. The 3-channel architecture
is targeted at high resolution RGB applications but can be used
in HD YPbPr applications as well.
The AD8124 is designed such that systems that use short-to-
medium-length cables do not pay a noise penalty for excess gain
that they do not require. The high gain is only available for
longer length systems where it is required. This feature is built
into the VPEAK control and is transparent to the user.
Three continuously adjustable control voltages, common
to the RGB channels, are available to the designer to provide
compensation for various cable lengths as well as for variations
in the cable itself. The VPEAK input is used to control the amount
of high frequency peaking. VPEAK is the primary control that is
used to compensate for frequency and cable-length dependent,
high frequency losses that are present due to the skin effect of
the cable. A second control pin, VGAIN, is used to adjust broadband
gain to compensate for low frequency flat losses present in the
cable. A third control, VPOLE, is used to move the positions of the
equalizer poles and can be linearly derived from VPEAK, as illustrated
in the Typical Performance Characteristics section and
Applications Information section, for UTP and coaxial cables.
Finally, an output offset adjust control, VOFFSET, allows the designer
to shift the output dc level.
Two comparators are provided on-chip that can be used for sync
pulse extraction in systems that use sync-on-common mode
encoding. Each comparator has very low output impedance and
can therefore be used in a source-only cable termination scheme
by placing a series resistor equal to the cable characteristic impedance
directly on the comparator output. Additional details are provided
in the Applications Information section.
INPUT COMMON-MODE VOLTAGE RANGE
CONSIDERATIONS
When using the AD8124 as a receiver, it is important to ensure
that its input common-mode voltage stays within the specified
range. The received common-mode level is calculated by adding
the common-mode level of the driver, the single-ended peak
amplitude of the received signal, the amplitude of any sync
pulses, and the other induced common-mode signals, such as
ground shifts between the driver and the AD8124 and pickup
from external sources, such as power lines and fluorescent lights.
See the Applications Information section for more details.
The AD8124 has a high impedance differential input that makes
termination simple and allows dc-coupled signals to be received
directly from the cable. The AD8124 input can also be used in a
single-ended fashion in coaxial cable applications.
The AD8124 has a low impedance output that is capable of driving
a 150 Ω load. For systems where the AD8124 has to drive a high
impedance capacitive load, it is recommended that a small series
resistor be placed between the output and load to buffer the
capacitance. The resistor should not be so large as to reduce
the overall bandwidth to an unacceptable level.
Rev. A | Page 10 of 15
Data Sheet
AD8124
APPLICATIONS INFORMATION
The comparator outputs have nearly 0 Ω output impedance and
are designed to drive source-terminated transmission lines. The
source termination technique uses a resistor in series with each
comparator output such that the sum of the comparator source
resistance (≈0 Ω) and the series resistor equals the transmission
line characteristic impedance. The load end of the transmission
line is high impedance. When the signal is launched into the source
termination, its initial value is one-half its source value because its
amplitude is divided by two in the voltage divider formed by the
source termination and the transmission line. At the load, the
signal experiences nearly 100% positive reflection due to the
high impedance load and is restored to nearly its full value. This
technique is commonly used in PCB layouts that involve high
speed digital logic.
BASIC OPERATION
The AD8124 is easy to apply because it contains everything
on-chip needed for cable loss compensation. Figure 19 shows a
basic application circuit (power supplies not shown) with common-
mode sync pulse extraction that is compatible with the common-
mode sync pulse encoding technique used in the AD8134, AD8142,
AD8147, and AD8148 triple differential drivers. If sync extraction
is not required, the terminations can be single 100 Ω resistors,
and the comparator inputs can be left floating. In Figure 19, the
AD8124 feeds a high impedance input, such as a delay line or
crosspoint switch, and the additional gain of two that makes up
for double termination loss is not required.
COMPARATORS
In addition to general-purpose applications, the two on-chip
comparators can be used to extract video sync pulses from the
received common-mode voltages or to receive differential digital
information. Built-in hysteresis helps to eliminate false triggers
from noise. The Sync Pulse Extraction Using Comparators
section describes the sync extraction details.
Figure 18 shows how to apply the comparators with source
termination when driving a 50 Ω transmission line that is high
impedance at its receive end.
HIGH-Z
49.9Ω
Z
= 50Ω
0
Figure 18. Using a Comparator with Source Termination
26
V
V
V
V
PEAK
POLE
GAIN
27
25
23
ANALOG
CONTROL
INPUTS
AD8124
OFFSET
28
POWER-DOWN
CONTROL
PD
RED
GREEN
BLUE
31
32
49.9Ω
49.9Ω
18
15
12
RECEIVED
RED VIDEO
RED VIDEO OUT
GREEN VIDEO OUT
BLUE VIDEO OUT
34
35
49.9Ω
49.9Ω
RECEIVED
GREEN VIDEO
37
38
49.9Ω
49.9Ω
RECEIVED
BLUE VIDEO
1kΩ
1kΩ
BLUE CMV
2
4
6
1
2
HSYNC OUT
VSYNC OUT
RED CMV 3
8
GREEN
CMV
475Ω
7
GND REFERENCE
24, 39
47pF
47pF
Figure 19. Basic Application Circuit with Common-Mode Sync Extraction
Rev. A | Page 11 of 15
AD8124
Data Sheet
In some cases, as would likely be with automatic control, the
SYNC PULSE EXTRACTION USING COMPARATORS
V
PEAK control is derived from a low impedance source, such as
The AD8124 is useful in many systems that transport computer
video signals, which typically comprise red, green, and blue (RGB)
video signals and separate horizontal and vertical sync signals.
Because the sync signals are separate and not embedded in the
color signals, it is advantageous to transmit them using a simple
scheme that encodes them among the three common-mode
voltages of the RGB signals. The AD8134, AD8142, AD8147, and
AD8148 triple differential drivers are natural complements to
the AD8124 because they perform the sync pulse encoding with
the necessary circuitry on-chip.
an op amp. Figure 20 shows how to derive VPOLE from VPEAK in a
UTP application according to the recommended curves shown
in Figure 16 when VPEAK originates from a low impedance source.
Clearly, the 5 V supply must be clean to provide a clean VPOLE
voltage.
20Ω
V
PEAK
5V
14kΩ
8.25kΩ
V
5.11kΩ
PEAK
V
PEAK
2
V
≈
+ 0.9V
POLE
The sync encoding equations follow:
Figure 20. Deriving VPOLE from VPEAK with Low-Z Source for the UTP Cable
K
2
Red VCM
V H
(1)
(2)
(3)
The 20 Ω series resistor in the VPEAK path provides capacitive load
buffering for the op amp. This value can be modified, depending
on the actual capacitive load.
K
2
Green VCM
2 V
In automatic equalization circuits that place the control voltages
inside feedback loops, attention must be paid to the poles produced
by the summing resistors and load capacitances.
K
2
Blue VCM
where:
V H
The peaking can also be adjusted by a mechanical or digitally
controlled potentiometer. In these cases, if the resistance of the
potentiometer is a couple of orders of magnitude lower than the
values of the resistors used to develop VPOLE, its resistance can be
ignored. Figure 21 shows how to use a 500 Ω potentiometer with
the resistor values shown in Figure 20 scaled up by a factor of 10.
Red VCM, Green VCM, and Blue VCM are the transmitted common-
mode voltages of the respective color signals.
K is an adjustable gain constant that is set by the driver.
V and H are the vertical and horizontal sync pulses, defined
with a weight of −1 when the pulses are in their low states and a
weight of +1 when they are in their high states.
V
PEAK
5V
The AD8134, AD8142, and AD8146/AD8147/AD8148 data
sheets contain further details regarding the encoding scheme.
Figure 19 illustrates how the AD8124 comparators can be used to
extract the horizontal and vertical sync pulses that are encoded on
the RGB common-mode voltages by the aforementioned drivers.
5V
750Ω
500Ω
140kΩ
51.1kΩ
V
PEAK
V
≈
+ 0.9V
POLE
2
82.5kΩ
Figure 21. Deriving VPOLE from VPEAK with a Potentiometer for the UTP Cable
USING THE VPEAK, VPOLE, VGAIN, AND VOFFSET INPUTS
Many potentiometers have wide tolerances. If a wide tolerance
potentiometer is used, it may be necessary to change the value
The VPEAK input is the main peaking control and is used to
compensate for the low-pass roll-off in the cable response. The
of the 750 Ω resistor to obtain a full swing for VPEAK
.
V
POLE input is a secondary frequency response shaping control
The VGAIN input is essentially a contrast control and can be set
by adjusting it to produce the correct amplitude of a known test
signal (such as a white screen) at the AD8124 output.
that shifts the positions of the equalizer poles. The VGAIN input
controls the wideband flat gain and is used to compensate for
the low frequency cable loss that is nominally flat. The VOFFSET
input is used to produce an offset at the AD8124 output. The
output offset is equal to the voltage applied to the VOFFSET input,
limited by the output swing limits.
VGAIN can also be derived from VPEAK according to the linear
relationships shown in Figure 16 and Figure 17. Figure 22 shows
how to derive VPOLE and VGAIN from VPEAK in a UTP application
that originates from a low-Z source.
The VPEAK and VPOLE controls can be used independently or they
can be coupled to form a single peaking control. While Figure 16
and Figure 17 show recommended settings vs. cable length,
designers may find other combinations that they prefer. These
two controls give designers extra freedom, as well as the ability
to compensate for different cable types (such as UTP and coaxial
cable), as opposed to having only a single frequency shaping
control.
20Ω
V
PEAK
5V
14kΩ
V
5.11kΩ
5.11kΩ
V
PEAK
PEAK
2
V
≈
+ 0.9V
POLE
8.25kΩ
5V
60.4kΩ
133kΩ
V
≈ 0.89 × V
+ 0.38V
GAIN
PEAK
Figure 22. Deriving VPOLE and VGAIN from VPEAK with Low-Z Source for the UTP Cable
Rev. A | Page 12 of 15
Data Sheet
AD8124
The other option is to include a triple gain-of-2 buffer, such as the
ADA4862-3, on the AD8124 RGB outputs, as shown in Figure 25
for one channel (power supplies not shown). The ADA4862-3
provides the gain of 2 that compensates for the double-
termination loss.
USING THE AD8124 WITH COAXIAL CABLE
The VPOLE control allows the AD8124 to be used with other
types of cable, including coaxial cable. Figure 17 presents the
recommended settings for VPEAK, VPOLE, and VGAIN when the
AD8124 is used with good quality 75 Ω video cable. Figure 23
shows how to derive VPOLE and VGAIN from VPEAK in a coaxial
cable application where VPEAK originates from a low-Z source.
20Ω
ONE CHANNEL OF ADA4862-3
ONE VIDEO
OUTPUT
FROM AD8124
75Ω
Z = 75Ω
0
500Ω
75Ω
500Ω
V
PEAK
24.3kΩ
Figure 25. Using the ADA4862-3 on AD8124 Outputs
V
5.11kΩ
1.16kΩ
PEAK
V
V
≈ 0.76 × V
– 0.41V
– 0.62V
POLE
PEAK
47.5kΩ
–5V
DRIVING A CAPACITIVE LOAD
20kΩ
When driving a high impedance capacitive input, it is necessary
to place a small series resistor between each of the three AD8124
video outputs and the load to buffer the input capacitance of the
device being driven. Clearly, the resistor value must be small
enough to preserve the required bandwidth.
≈ 1.06 × V
10kΩ
GAIN
PEAK
+5V
1.24kΩ
Figure 23. Deriving VPOLE and VGAIN from VPEAK with Low-Z Source for the Coaxial Cable
POWER SUPPLY FILTERING
The op amp in the circuit that develops VGAIN is required to insert
the offset of −0.62 V with a gain from VPEAK to VGAIN that is close to
unity. A passive offset circuit requires an offset injection voltage
that is much larger in magnitude than the available −5 V supply.
Clearly, the VGAIN control voltage can also be developed
independently.
External power supply filtering between the system power supplies
and the AD8124 is recommended in most applications to prevent
supply noise from contaminating the received signal as well as
to prevent unwanted feedback through the supplies that may
cause instability. Figure 26 shows that the AD8124 power supply
rejection decreases with increasing frequency. These plots are
for the lowest control settings and shift upward as the peaking
is increased.
The AD8124 differential input can accept signals carried over
unbalanced cable, as shown in Figure 24, for an unbalanced
75 Ω coaxial cable termination.
10
AD8124
V
V
V
= 0V
= 0V
= 0V
GAIN
PEAK
POLE
INPUT STAGE
INPUT FROM
75Ω CABLE
0
–10
–20
–30
–40
–50
–60
75Ω
Figure 24. Terminating a 75 Ω Cable
DRIVING 75 Ω VIDEO CABLE WITH THE AD8124
When the RGB outputs must drive a 75 Ω line rather than a
high impedance load, an additional gain of two is required to
make up for the double termination loss (75 Ω source and load
terminations). There are two options available for this.
+PSRR
–PSRR
One option is to place the additional gain of 2 at the drive end
by using the AD8148 triple differential driver to drive the cable.
The AD8148 has a fixed gain of 4 instead of the usual gain of 2
and thereby provides the required additional gain of 2 without
having to add additional amplifiers to the signal chain. The
AD8148 also contains sync-on-common-mode encoding. If
sync-on-common-mode is not required, it can be deactivated
on the AD8148 by connecting its sync level input to ground.
100k
1M
10M
100M
FREQUENCY (Hz)
Figure 26. PSRR vs. Frequency
Rev. A | Page 13 of 15
AD8124
Data Sheet
A suitable filter that uses a surface-mount ferrite bead is shown
in Figure 27, and its frequency response is shown in Figure 28.
Because the frequency response was taken using a 50 Ω network
analyzer and with only one 0.1 μF capacitor on the AD8124 side,
the actual amount of rejection provided by the filter in a real-world
application is different from that shown in Figure 28. The general
shape of the rejection curve, however, matches Figure 28, providing
substantially increased overall PSRR from approximately 5 MHz to
500 MHz, where it is most needed. One filter is required on each
of the two supplies (not one filter per supply pin).
LAYOUT AND POWER SUPPLY DECOUPLING
CONSIDERATIONS
Standard high speed PCB layout practices should be adhered
to when designing with the AD8124. A solid ground plane is
required and controlled impedance traces should be used when
interconnecting the high speed signals. Source termination resistors
on all outputs must be placed as close as possible to the output pins.
The exposed paddle on the underside of the AD8124 must be
connected to a pad that connects to at least one PCB plane.
Several thermal vias should be used to make the connection
between the pad and the plane(s).
FAIR-RITE
2743021447
SYSTEM
SUPPLY
TO AD8124*
High quality 0.1 μF power supply decoupling capacitors should
be placed as close as possible to all supply pins. Small surface-
mount ceramic capacitors should be used, and tantalum capacitors
are recommended for bulk supply decoupling.
0.1µF
4700pF
4700pF
*ALL AD8124 SUPPLY PINS ARE INDIVIDUALLY
DECOUPLED WITH A 0.1µF CAPACITOR.
Figure 27. Power Supply Filter
POWER-DOWN
0
The power-down feature is intended to be used to reduce power
consumption when a particular device is not in use and does
not place the output in a high-Z state when asserted. The input
logic levels and supply current in power-down mode are presented
in the Power Supply section of Table 1.
–20
–40
–60
–80
–100
–120
10k
100k
1M
10M
100M
FREQUENCY (Hz)
Figure 28. Power Supply Filter Frequency Response in a 50 Ω System
Rev. A | Page 14 of 15
Data Sheet
AD8124
OUTLINE DIMENSIONS
6.10
6.00 SQ
5.90
0.30
0.23
0.18
PIN 1
INDICATOR
PIN 1
INDICATOR
31
30
40
1
0.50
BSC
4.45
4.30 SQ
4.25
EXPOSED
PAD
21
20
10
11
0.45
0.40
0.35
0.25 MIN
TOP VIEW
BOTTOM VIEW
FOR PROPER CONNECTION OF
THE EXPOSED PAD, REFER TO
THE PIN CONFIGURATION AND
FUNCTION DESCRIPTIONS
0.80
0.75
0.70
0.05 MAX
0.02 NOM
SECTION OF THIS DATA SHEET.
COPLANARITY
0.08
0.20 REF
SEATING
PLANE
COMPLIANT TO JEDEC STANDARDS MO-220-WJJD.
Figure 29. 40-Lead Lead Frame Chip Scale Package [LFCSP]
6 mm × 6 mm Body and 0.75 mm Package Height
(CP-40-10)
Dimensions shown in millimeters
ORDERING GUIDE
Model1
Temperature Range
−40°C to +85°C
−40°C to +85°C
−40°C to +85°C
Package Description
Package Option
AD8124ACPZ
AD8124ACPZ-R7
AD8124ACPZ-RL
40-Lead Lead Frame Chip Scale Package [LFCSP]
40-Lead Lead Frame Chip Scale Package [LFCSP]
40-Lead Lead Frame Chip Scale Package [LFCSP]
CP-40-10
CP-40-10
CP-40-10
1 Z = RoHS Compliant Part.
©2011–2015 Analog Devices, Inc. All rights reserved. Trademarks and
registered trademarks are the property of their respective owners.
D09601-0-12/15(A)
Rev. A | Page 15 of 15
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