ADL5380ACPZ-R7 [ADI]
400 MHz to 6 GHz Quadrature Demodulator; 400 MHz至6 GHz的正交解调器
| 型号： | ADL5380ACPZ-R7 |
| 厂家： | 
ADI |
| 描述： | 400 MHz to 6 GHz Quadrature Demodulator |
| 文件： | 总36页 (文件大小：843K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
400 MHz to 6 GHz
Quadrature Demodulator
ADL5380
FEATURES
FUNCTIONAL BLOCK DIAGRAM
ENBL ADJ
Operating RF and LO frequency: 400 MHz to 6 GHz
Input IP3
ADL5380
IHI
BIAS
30 dBm @ 900 MHz
28 dBm @1900 MHz
Input IP2: >65 dBm @ 900 MHz
Input P1dB (IP1dB): 11.6 dBm @ 900 MHz
Noise figure (NF)
ILO
LOIP
10.9 dB @ 900 MHz
11.7 dB @ 1900 MHz
Voltage conversion gain: ~7 dB
Quadrature demodulation accuracy @ 900 MHz
Phase accuracy: ~0.2°
RFIN
RFIP
QUADRATURE
PHASE SPLITTER
V2I
LOIN
QHI
Amplitude balance: ~0.07 dB
Demodulation bandwidth: ~390 MHz
Baseband I/Q drive: 2 V p-p into 200 Ω
Single 5 V supply
QLO
Figure 1.
APPLICATIONS
Cellular W-CDMA/GSM/LTE
Microwave point-to-(multi)point radios
Broadband wireless and WiMAX
GENERAL DESCRIPTION
The ADL5380 is a broadband quadrature I-Q demodulator that
covers an RF/IF input frequency range from 400 MHz to 6 GHz.
With a NF = 10.9 dB, IP1dB = 11.6 dBm, and IIP3 = 29.7 dBm @
900 MHz, the ADL5380 demodulator offers outstanding dynamic
range suitable for the demanding infrastructure direct-conversion
requirements. The differential RF inputs provide a well-behaved
broadband input impedance of 50 Ω and are best driven from a
1:1 balun for optimum performance.
The fully balanced design minimizes effects from second-order
distortion. The leakage from the LO port to the RF port is
<−50 dBm. Differential dc offsets at the I and Q outputs are
typically <20 mV. Both of these factors contribute to the
excellent IIP2 specification, which is >65 dBm.
The ADL5380 operates off a single 4.75 V to 5.25 V supply. The
supply current is adjustable by placing an external resistor from
the ADJ pin to either the positive supply, VS, (to increase supply
current and improve IIP3) or to ground (which decreases supply
current at the expense of IIP3).
Excellent demodulation accuracy is achieved with amplitude
and phase balances of ~0.07 dB and ~0.2°, respectively. The
demodulated in-phase (I) and quadrature (Q) differential outputs
are fully buffered and provide a voltage conversion gain of ~7 dB.
The buffered baseband outputs are capable of driving a 2 V p-p
differential signal into 200 Ω.
The ADL5380 is fabricated using the Analog Devices, Inc.,
advanced silicon-germanium bipolar process and is available
in a 24-lead exposed paddle LFCSP.
Rev. 0
Information furnished by Analog Devices is believed to be accurate and reliable. However, no
responsibility is assumed by Analog Devices for its use, nor for any infringements of patents or other
rights of third parties that may result from its use. Specifications subject to change without notice. No
license is granted by implication or otherwise under any patent or patent rights of Analog Devices.
Trademarks and registeredtrademarks arethe property of their respective owners.
One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A.
Tel: 781.329.4700
Fax: 781.461.3113
www.analog.com
©2009 Analog Devices, Inc. All rights reserved.
ADL5380
TABLE OF CONTENTS
Features .............................................................................................. 1
V-to-I Converter......................................................................... 22
Mixers .......................................................................................... 22
Emitter Follower Buffers ........................................................... 22
Bias Circuit.................................................................................. 22
Applications Information.............................................................. 23
Basic Connections...................................................................... 23
Power Supply............................................................................... 23
Local Oscillator (LO) Input ...................................................... 23
RF Input....................................................................................... 24
Baseband Outputs ...................................................................... 24
Error Vector Magnitude (EVM) Performance........................... 24
Low IF Image Rejection............................................................. 25
Example Baseband Interface..................................................... 26
Characterization Setups................................................................. 30
Evaluation Board ............................................................................ 32
Thermal Grounding and Evaluation Board Layout............... 34
Outline Dimensions....................................................................... 35
Ordering Guide .......................................................................... 35
Applications....................................................................................... 1
Functional Block Diagram .............................................................. 1
General Description......................................................................... 1
Revision History ............................................................................... 2
Specifications..................................................................................... 3
Absolute Maximum Ratings............................................................ 5
ESD Caution.................................................................................. 5
Pin Configuration and Function Descriptions............................. 6
Typical Performance Characteristics ............................................. 7
Low Band Operation.................................................................... 7
Midband Operation ................................................................... 11
High Band Operation ................................................................ 14
Distributions for fLO = 900 MHz............................................... 17
Distributions for fLO = 1900 MHz............................................. 18
Distributions for fLO = 2700 MHz............................................. 19
Distributions for fLO = 3600 MHz............................................. 20
Distributions for fLO = 5800 MHz............................................. 21
Circuit Description......................................................................... 22
LO Interface................................................................................. 22
REVISION HISTORY
7/09—Revision 0: Initial Version
Rev. 0 | Page 2 of 36
ADL5380
SPECIFICATIONS
VS = 5 V, TA = 25°C, fLO = 900 MHz, fIF = 4.5 MHz, PLO = 0 dBm, ZO = 50 ꢀ, unless otherwise noted. Baseband outputs differentially
loaded with 450 ꢀ. Loss of the balun used to drive the RF port was de-embedded from these measurements.
Table 1.
Parameter
Condition
Min Typ
Max Unit
OPERATING CONDITIONS
LO and RF Frequency Range
LO INPUT
0.4
6
GHz
LOIP, LOIN
Input Return Loss
LO driven differentially through a balun at 900 MHz
−10
dB
LO Input Level
−6
0
+6
dBm
I/Q BASEBAND OUTPUTS
Voltage Conversion Gain
QHI, QLO, IHI, ILO
450 Ω differential load on I and Q outputs at 900 MHz
200 Ω differential load on I and Q outputs at 900 MHz
1 V p-p signal, 3 dB bandwidth
At 900 MHz
6.9
5.9
390
0.2
0.07
10
dB
dB
MHz
Degrees
dB
Demodulation Bandwidth
Quadrature Phase Error
I/Q Amplitude Imbalance
Output DC Offset (Differential)
Output Common Mode
0 dBm LO input at 900 MHz
Dependent on ADJ pin setting
mV
VADJ ~ 4 V (set by 1.5 kΩ from ADJ pin to VS)
VADJ ~ 4.8 V (set by 200 Ω from ADJ pin to VS)
VADJ ~ 2.4 V (ADJ pin open)
VS − 2.5
VS − 2.8
VS − 1.2
37
2
12
V
V
V
MHz
V p-p
mA
0.1 dB Gain Flatness
Output Swing
Peak Output Current
POWER SUPPLIES
Voltage
Differential 200 Ω load
Each pin
VS = VCC1, VCC2, VCC3
4.75
5.25
V
Current
1.5 kΩ from ADJ pin to VS; ENBL pin low
1.5 kΩ from ADJ pin to VS; ENBL pin high
Pin ENBL
245
145
mA
mA
ENABLE FUNCTION
Off Isolation
−70
45
950
dB
ns
ns
V
Turn-On Settling Time
Turn-Off Settling Time
ENBL High Level (Logic 1)
ENBL Low Level (Logic 0)
DYNAMIC PERFORMANCE at RF = 900 MHz
Conversion Gain
ENBL high to low
ENBL low to high
2.5
1.7
V
VADJ ~ 4 V (set by 1.5 kΩ from ADJ pin to VS)
6.9
dB
Input P1dB
11.6
−19
68
29.7
−52
−67
0.07
0.2
dBm
dB
RF Input Return Loss
Second-Order Input Intercept (IIP2)
Third-Order Input Intercept (IIP3)
LO to RF
RF to LO
IQ Magnitude Imbalance
IQ Phase Imbalance
RFIP, RFIN driven differentially through a balun
−5 dBm each input tone
−5 dBm each input tone
RFIN, RFIP terminated in 50 Ω
LOIN, LOIP terminated in 50 Ω
dBm
dBm
dBm
dBc
dB
Degrees
dB
dB
Noise Figure
Noise Figure Under Blocking Conditions
10.9
13.1
With a −5 dBm input interferer 5 MHz away
Rev. 0 | Page 3 of 36
ADL5380
Parameter
Condition
Min Typ
Max Unit
DYNAMIC PERFORMANCE at RF = 1900 MHz
VADJ ~ 4 V (set by 1.5 kΩ from ADJ pin to VS)
Conversion Gain
6.8
dB
Input P1dB
11.6
−13
61
dBm
dB
RF Input Return Loss
Second-Order Input Intercept (IIP2)
Third-Order Input Intercept (IIP3)
LO to RF
RF to LO
IQ Magnitude Imbalance
IQ Phase Imbalance
RFIP, RFIN driven differentially through a balun
−5 dBm each input tone
dBm
dBm
dBm
dBc
dB
Degrees
dB
dB
−5 dBm each input tone
RFIN, RFIP terminated in 50 Ω
LOIN, LOIP terminated in 50 Ω
27.8
−49
−77
0.07
0.25
11.7
14
Noise Figure
Noise Figure Under Blocking Conditions
DYNAMIC PERFORMANCE at RF = 2700 MHz
Conversion Gain
With a −5 dBm input interferer 5 MHz away
VADJ ~ 4 V (set by 1.5 kΩ from ADJ pin to VS)
7.4
dB
Input P1dB
11
−10
54
dBm
dB
dBm
dBm
dBm
dBc
dB
Degrees
dB
RF Input Return Loss
Second-Order Input Intercept (IIP2)
Third-Order Input Intercept (IIP3)
LO to RF
RF to LO
IQ Magnitude Imbalance
IQ Phase Imbalance
RFIP, RFIN driven differentially through a balun
−5 dBm each input tone
−5 dBm each input tone
RFIN, RFIP terminated in 50 Ω
LOIN, LOIP terminated in 50 Ω
28
−49
−73
0.07
0.5
Noise Figure
12.3
DYNAMIC PERFORMANCE at RF = 3600 MHz
Conversion Gain
VADJ ~ 4.8 V (set by200 Ω from ADJ pin to VS)
6.3
dB
Input P1dB
9.6
−11
48
dBm
dB
RF Input Return Loss
Second-Order Input Intercept (IIP2)
Third-Order Input Intercept (IIP3)
LO to RF
RF to LO
IQ Magnitude Imbalance
IQ Phase Imbalance
RFIP, RFIN driven differentially through a balun
−5 dBm each input tone
−5 dBm each input tone
RFIN, RFIP terminated in 50 Ω
LOIN, LOIP terminated in 50 Ω
dBm
dBm
dBm
dBc
dB
Degrees
dB
dB
21
−46
−72
0.14
1.1
14.2
16.2
Noise Figure
Noise Figure Under Blocking Conditions
DYNAMIC PERFORMANCE at RF = 5800 MHz
Conversion Gain
With a −5 dBm input interferer 5 MHz away
VADJ ~ 2.4 V (ADJ pin left open)
5.8
dB
Input P1dB
8.2
−7.5
44
20.6
−47
−62
0.07
−1.25
15.5
18.9
dBm
dB
RF Input Return Loss
Second-Order Input Intercept (IIP2)
Third-Order Input Intercept (IIP3)
LO to RF
RF to LO
IQ Magnitude Imbalance
IQ Phase Imbalance
RFIP, RFIN driven differentially through a balun
−5 dBm each input tone
−5 dBm each input tone
RFIN, RFIP terminated in 50 Ω
LOIN, LOIP terminated in 50 Ω
dBm
dBm
dBm
dBc
dB
Degrees
dB
dB
Noise Figure
Noise Figure Under Blocking Conditions
With a −5 dBm input interferer 5 MHz away
Rev. 0 | Page 4 of 36
ADL5380
ABSOLUTE MAXIMUM RATINGS
Table 2.
Parameter
Stresses above those listed under Absolute Maximum Ratings
may cause permanent damage to the device. This is a stress
rating only; functional operation of the device at these or any
other conditions above those indicated in the operational
section of this specification is not implied. Exposure to absolute
maximum rating conditions for extended periods may affect
device reliability.
Rating
Supply Voltage: VCC1, VCC2, VCC3
LO Input Power
5.5 V
13 dBm (re: 50 Ω)
15 dBm (re: 50 Ω)
1370 mW
RF Input Power
Internal Maximum Power Dissipation
1
θJA
53°C/W
Maximum Junction Temperature
Operating Temperature Range
Storage Temperature Range
150°C
−40°C to +85°C
−65°C to +125°C
ESD CAUTION
1 Per JDEC standard JESD 51-2. For information on optimizing thermal
impedance, see the Thermal Grounding and Evaluation Board Layout
section.
Rev. 0 | Page 5 of 36
ADL5380
PIN CONFIGURATION AND FUNCTION DESCRIPTIONS
PIN 1
INDICATOR
GND3
GND1
IHI
ILO
GND1
1
2
3
4
5
6
18 GND3
17 GND2
16 QHI
15 QLO
14 GND2
13 VCC2
ADL5380
TOP VIEW
(Not to Scale)
VCC1
NOTES
1. NC = NO CONNECT.
2. THE EXPOSED PAD SHOULD BE CONNECTED TO A
LOW IMPEDANCE THERMAL AND ELECTRICAL
GROUND PLANE.
Figure 2. Pin Configuration
Table 3. Pin Function Descriptions
Pin No. Mnemonic
Description
1, 2, 5, 8, 11, 14, GND1, GND2, GND3, GND4 Ground Connect.
17, 18, 20, 23
3, 4, 15, 16
IHI, ILO, QLO, QHI
I Channel and Q Channel Mixer Baseband Outputs. These outputs have a 50 Ω differential
output impedance (25 Ω per pin). Each output pair can swing 2 V p-p (differential) into a
load of 200 Ω. The output 3 dB bandwidth is ~400 MHz.
6, 13, 24
7
VCC1, VCC2, VCC3
ENBL
Supply. Positive supply for LO, IF, biasing, and baseband sections. Decouple these pins to
the board ground using the appropriate-sized capacitors.
Enable Control. When pulled low, the part is fully enabled; when pulled high, the part is
partially powered down and the output is disabled.
9, 10
LOIP, LOIN
Local Oscillator Input. Pins must be ac-coupled. A differential drive through a balun is
necessary to achieve optimal performance. Recommended balun is the Mini-Circuits
TC1-1-13 for lower frequencies, the Johanson Technology 3600 balun for midband
frequencies, and the Johanson Technology 5400 balun for high band frequencies.
Balun choice depends on the desired frequency range of operation.
12
19
NC
ADJ
Do not connect this pin.
A resistor to VS that optimizes third-order intercept. For operation <3 GHz, RADJ = 1.5 kΩ.
For operation from 3 GHz to 4 GHz, RADJ = 200 Ω. For operation >5 GHz, RADJ = open.
See the Circuit Description section for more details.
21, 22
RFIN, RFIP
RF Input. A single-ended 50 Ω signal can be applied differentially to the RF inputs through
a 1:1 balun. Recommended balun is the Mini-Circuits TC1-1-13 for lower frequencies, the
Johanson Technology 3600 balun for midband frequencies, and the Johanson Technology
5400 balun for high band frequencies. Balun choice depends on the desired frequency
range of operation.
EP
Exposed Paddle. Connect to a low impedance thermal and electrical ground plane.
Rev. 0 | Page 6 of 36
ADL5380
TYPICAL PERFORMANCE CHARACTERISTICS
VS = 5 V, TA = 25°C, LO drive level = 0 dBm, RF input balun loss is de-embedded, unless otherwise noted.
LOW BAND OPERATION
RF = 400 MHz to 3 GHz; Mini-Circuits TC1-1-13 balun on LO and RF inputs, 1.5 kꢀ from the ADJ pin to VS.
18
16
14
12
10
8
1.0
T
T
T
= –40°C
= +25°C
= +85°C
A
A
A
0.8
0.6
INPUT P1dB
0.4
0.2
0
GAIN
–0.2
–0.4
–0.6
–0.8
–1.0
6
T
T
T
= –40°C
= +25°C
= +85°C
A
A
A
4
2
LO FREQUENCY (MHz)
LO FREQUENCY (MHz)
Figure 3. Conversion Gain and Input 1 dB Compression Point (IP1dB) vs.
LO Frequency
Figure 5. IQ Gain Mismatch vs. LO Frequency
80
2
1
I CHANNEL
Q CHANNEL
70
0
60
–1
–2
–3
–4
–5
–6
–7
–8
INPUT IP2
50
40
INPUT IP3 (I AND Q CHANNELS)
30
20
10
T
T
T
= –40°C
= +25°C
= +85°C
A
A
A
10
100
1000
BASEBAND FREQUENCY (MHz)
LO FREQUENCY (MHz)
Figure 6. Normalized IQ Baseband Frequency Response
Figure 4. Input Third-Order Intercept (IIP3) and
Input Second-Order Intercept Point (IIP2) vs. LO Frequency
Rev. 0 | Page 7 of 36
ADL5380
35
30
25
20
15
10
5
300
280
260
240
220
200
180
160
18
T
T
T
= –40°C
= +25°C
= +85°C
T
T
T
= –40°C
= +25°C
= +85°C
A
A
A
A
A
A
17
16
15
14
13
12
11
10
9
INPUT IP3
SUPPLY
CURRENT
NOISE FIGURE
8
0
1.0
1.5
2.0
2.5
3.0
3.5
4.0
4.5
V
(V)
ADJ
LO FREQUENCY (MHz)
Figure 7. Noise Figure vs. LO Frequency
Figure 10. IIP3, Noise Figure, and Supply Current vs. VADJ, fLO = 900 MHz
4
3
2
1
0
25
23
21
19
17
15
13
1920MHz
–1
T
T
T
= –40°C
= +25°C
= +85°C
11
A
A
A
920MHz
–2
–3
–4
9
7
5
–30
–25
–20
–15
–10
–5
0
5
RF BLOCKER INPUT POWER (dBm)
LO FREQUENCY (MHz)
Figure 8. IQ Quadrature Phase Error vs. LO Frequency
Figure 11. Noise Figure vs. Input Blocker Level, fLO = 900 MHz, fLO = 1900 MHz
(RF Blocker 5 MHz Offset)
20
18
16
14
12
10
8
75
70
65
60
55
50
45
40
35
30
25
18
16
14
12
10
8
60
55
50
45
40
35
30
25
20
IIP2, I CHANNEL
IIP2, Q CHANNEL
IIP2, Q CHANNEL
IIP2, I CHANNEL
NOISE FIGURE
IP1dB
IP1dB
GAIN
NOISE FIGURE
GAIN
6
6
4
IIP3
IIP3
4
2
2
0
–6 –5 –4 –3 –2 –1
0
1
2
3
4
5
6
–6 –5 –4 –3 –2 –1
0
1
2
3
4
5
6
LO LEVEL (dBm)
LO LEVEL (dBm)
Figure 12. Conversion Gain, IP1dB, Noise Figure, IIP3, and IIP2 vs.
LO Level, fLO = 2700 MHz
Figure 9. Conversion Gain, IP1dB, Noise Figure, IIP3, and IIP2 vs.
LO Level, fLO = 900 MHz
Rev. 0 | Page 8 of 36
ADL5380
35
30
25
20
15
10
5
0
–5
T
T
T
= –40°C
= +25°C
= +85°C
A
A
A
INPUT IP3
–10
–15
–20
–25
NOISE FIGURE
0
1.0
1.5
2.0
2.5
3.0
(V)
3.5
4.0
4.5
0.4 0.6 0.8 1.0 1.2 1.4 1.6 1.8 2.0 2.2 2.4 2.6 2.8 3.0
RF FREQUENCY (GHz)
V
ADJ
Figure 13. IIP3 and Noise Figure vs. VADJ, fLO = 2700 MHz
Figure 16. RF Port Return Loss vs. RF Frequency Measured on
Characterization Board Through TC1-1-13 Balun
80
–20
70
60
50
40
30
20
10
0
–30
–40
–50
–60
–70
–80
–90
–100
900MHz: GAIN
900MHz: IP1dB
900MHz: IIP2, I CHANNEL
900MHz: IIP2, Q CHANNEL
2700MHz: GAIN
2700MHz: IP1dB
2700MHz: IIP2, I CHANNEL
2700MHz: IIP2, Q CHANNEL
1
2
3
4
0.4 0.6 0.8 1.0 1.2 1.4 1.6 1.8 2.0 2.2 2.4 2.6 2.8 3.0
LO FREQUENCY (GHz)
V
(V)
ADJ
Figure 14. Conversion Gain, IP1dB, and IIP2 vs.
VADJ, fLO = 900 MHz, fLO = 2700 MHz
Figure 17. LO-to-RF Leakage vs. LO Frequency
40
35
30
25
20
15
10
5
90
85
80
75
70
65
60
55
50
–20
–30
–40
–50
–60
–70
–80
–90
–100
T
T
T
= –40°C
= +25°C
= +85°C
A
A
A
I CHANNEL
Q CHANNEL
IIP3
IIP2
IP1dB
0
4.5
6.5
8.5
10.5
12.5
14.5
16.5
18.5
0.4 0.6 0.8 1.0 1.2 1.4 1.6 1.8 2.0 2.2 2.4 2.6 2.8 3.0
BASEBAND FREQUENCY (MHz)
RF FREQUENCY (GHz)
Figure 15. IP1dB, IIP3, and IIP2 vs. Baseband Frequency
Figure 18. RF-to-LO Leakage vs. RF Frequency
Rev. 0 | Page 9 of 36
ADL5380
0
–2
–4
–6
–8
–10
–12
–14
–16
0.4 0.6 0.8 1.0 1.2 1.4 1.6 1.8 2.0 2.2 2.4 2.6 2.8 3.0
LO FREQUENCY (GHz)
Figure 19. LO Port Return Loss vs. LO Frequency Measured on
Characterization Board Through TC1-1-13 Balun
Rev. 0 | Page 10 of 36
ADL5380
MIDBAND OPERATION
RF = 3 GHz to 4 GHz; Johanson Technology 3600BL14M050T balun on LO and RF inputs, 200 ꢀ from VADJ to VS.
14
13
12
11
10
9
20
18
16
14
12
10
8
60
55
50
45
40
35
30
25
20
15
10
T
T
T
= –40°C
= +25°C
= +85°C
A
A
A
IIP2, Q CHANNEL
IIP2, I CHANNEL
IP1dB
NOISE FIGURE
IP1dB
8
GAIN
GAIN
7
6
4
6
IIP3
2
5
0
4
–6 –5 –4 –3 –2 –1
0
1
2
3
4
5
6
3.0
3.1
3.2
3.3
3.4
3.5
3.6
3.7
3.8
3.9
4.0
LO LEVEL (dBm)
LO FREQUENCY (GHz)
Figure 20. Conversion Gain and Input 1 dB Compression Point (IP1dB) vs.
LO Frequency
Figure 23. Conversion Gain, IP1dB, Noise Figure, IIP3, and IIP2 vs.
LO Level, fLO = 3600 MHz
80
18
17
16
15
14
13
T
T
T
= –40°C
= +25°C
= +85°C
A
A
A
70
60
50
40
30
20
10
I CHANNEL
Q CHANNEL
INPUT IP2
12
11
10
9
T
T
T
= –40°C
= +25°C
= +85°C
A
A
A
INPUT IP3 I AND Q CHANNELS
8
3.0
3.1
3.2
3.3
3.4
3.5
3.6
3.7
3.8
3.9
4.0
3.0
3.1
3.2
3.3
3.4
3.5
3.6
3.7
3.8
3.9
4.0
LO FREQUENCY (GHz)
LO FREQUENCY (GHz)
Figure 24. Noise Figure vs. LO Frequency
Figure 21. Input Third-Order Intercept (IIP3) and
Input Second-Order Intercept Point (IIP2) vs. LO Frequency
4
3
2
1
0
1.0
T
T
T
= –40°C
= +25°C
= +85°C
A
A
A
T
T
T
= –40°C
= +25°C
= +85°C
0.8
0.6
A
A
A
0.4
0.2
0
–0.2
–0.4
–0.6
–0.8
–1.0
–1
–2
–3
–4
3.0
3.1
3.2
3.3
3.4
3.5
3.6
3.7
3.8
3.9
4.0
3.0
3.2
3.4
3.6
3.8
4.0
LO FREQUENCY (GHz)
LO FREQUENCY (GHz)
Figure 25. IQ Quadrature Phase Error vs. LO Frequency
Figure 22. IQ Gain Mismatch vs. LO Frequency
Rev. 0 | Page 11 of 36
ADL5380
30
300
280
260
240
220
200
180
–20
T
T
T
= –40°C
= +25°C
= +85°C
A
A
A
25
–30
–40
–50
–60
–70
–80
INPUT IP3
20
15
10
5
NOISE FIGURE
SUPPLY CURRENT
0
1.0
1.5
2.0
2.5
3.0
(V)
3.5
4.0
4.5
3.1
3.2
3.3
3.4
3.5
3.6
3.7
3.8
3.9
4.0
LO FREQUENCY (GHz)
V
ADJ
Figure 29. LO-to-RF Leakage vs. LO Frequency
Figure 26. IIP3, Noise Figure, and Supply Current vs. VADJ, fLO = 3600 MHz
–20
–30
–40
–50
–60
–70
–80
–90
–100
25
23
21
19
17
15
13
11
3.1
3.2
3.3
3.4
3.5
3.6
3.7
3.8
3.9
4.0
–30
–25
–20
–15
–10
–5
0
5
RF FREQUENCY (GHz)
RF POWEL LEVEL (dBm)
Figure 30. RF-to-LO Leakage vs. RF Frequency
Figure 27. Noise Figure vs. Input Blocker Level, fLO = 3600 MHz
(RF Blocker 5 MHz Offset)
0
–2
80
70
60
50
–4
40
3600MHz: GAIN
–6
3600MHz: IP1dB
3600MHz: IIP2, I CHANNEL
30
3600MHz: IIP2, Q CHANNEL
–8
20
10
0
–10
–12
–10
3.1
3.2
3.3
3.4
3.5
3.6
3.7
3.8
3.9
4.0
1
2
3
4
RF FREQUENCY (GHz)
V
(V)
ADJ
Figure 31. RF Port Return Loss vs. RF Frequency Measured on
Characterization Board Through Johanson Technology 3600 Balun
Figure 28. Conversion Gain, IP1dB, and IIP2 vs. VADJ, fLO = 3600 MHz
Rev. 0 | Page 12 of 36
ADL5380
0
–5
–10
–15
–20
–25
–30
3.1
3.2
3.3
3.4
3.5
3.6
3.7
3.8
3.9
4.0
LO FREQUENCY (GHz)
Figure 32. LO Port Return Loss vs. LO Frequency Measured on
Characterization Board Through Johanson Technology 3600 Balun
Rev. 0 | Page 13 of 36
ADL5380
HIGH BAND OPERATION
RF = 5 GHz to 6 GHz; Johanson Technology 5400BL15B050E balun on LO and RF inputs, the ADJ pin is open.
60
55
50
45
40
35
30
25
20
15
10
20
18
16
14
12
10
8
12
11
10
9
NOISE FIGURE
IIP2, Q CHANNEL
INPUT P1dB
IIP2, I CHANNEL
8
7
GAIN
IP1dB
GAIN
6
6
5
4
4
T
T
T
= –40°C
= +25°C
= +85°C
A
A
A
IIP3
2
3
0
2
–6 –5 –4 –3
–2 –1
0
1
2
3
4
5
6
5.1
5.2
5.3
5.4
5.5
5.6
5.7
5.8
5.9
6.0
LO LEVEL (dBm)
LO FREQUENCY (GHz)
Figure 33. Conversion Gain and Input 1 dB Compression Point (IP1dB) vs.
LO Frequency
Figure 36. Conversion Gain, IP1dB, Noise Figure, IIP3, and IIP2 vs.
LO Level, fLO = 5800 MHz
20
80
T
T
T
= –40°C
= –25°C
= +85°C
A
A
A
19
18
17
16
15
14
13
12
11
10
9
T
T
T
= –40°C
= +25°C
= +85°C
A
A
A
I CHANNEL
Q CHANNEL
70
60
50
40
30
20
10
INPUT IP2
INPUT IP3 (I AND Q CHANNELS)
8
5.0
5.1
5.2
5.3
5.4
5.5
5.6
5.7
5.8
5.9
6.0
5.1
5.2
5.3
5.4
5.5
5.6
5.7
5.8
5.9
6.0
LO FREQUENCY (GHz)
LO FREQUENCY (GHz)
Figure 37. Noise Figure vs. LO Frequency
Figure 34. Input Third-Order Intercept (IIP3) and
Input Second-Order Intercept Point (IIP2) vs. LO Frequency
4
3
1.0
0.8
T
T
T
= –40°C
= +25°C
= +85°C
A
A
A
T
T
T
= –40°C
= +25°C
= +85°C
A
A
A
0.6
2
0.4
1
0.2
0
0
–0.2
–0.4
–0.6
–0.8
–1.0
–1
–2
–3
–4
5.1
5.2
5.3
5.4
5.5
5.6
5.7
5.8
5.9
6.0
5.1
5.2
5.3
5.4
5.5
5.6
5.7
5.8
5.9
6.0
LO FREQUENCY (GHz)
LO FREQUENCY (GHz)
Figure 35. IQ Gain Mismatch vs. LO Frequency
Figure 38. IQ Quadrature Phase Error vs. LO Frequency
Rev. 0 | Page 14 of 36
ADL5380
30
25
20
15
10
5
300
280
260
240
220
200
180
–20
–30
–40
–50
–60
–70
–80
–90
–100
T
T
T
= –40°C
= +25°C
= +85°C
A
A
A
INPUT IP3
NOISE FIGURE
SUPPLY CURRENT
0
1.0
1.5
2.0
2.5
3.0
(V)
3.5
4.0
4.5
5.1
5.2
5.3
5.4
5.5
5.6
5.7
5.8
5.9
5.9
5.9
6.0
6.0
6.0
LO FREQUENCY (GHz)
V
ADJ
Figure 42. LO-to-RF Leakage vs. LO Frequency
Figure 39. IIP3, Noise Figure, and Supply Current vs. VADJ, fLO = 5800 MHz
–20
–30
–40
–50
–60
–70
–80
–90
–100
25
20
15
10
5
0
–30
5.1
5.2
5.3
5.4
5.5
5.6
5.7
5.8
–25
–20
–15
–10
–5
RF FREQUENCY (MHz)
RF POWER LEVEL (dBm)
Figure 40. Noise Figure vs. Input Blocker Level, fLO = 5800 MHz
(RF Blocker 5 MHz Offset)
Figure 43. RF-to-LO Leakage vs. RF Frequency
60
0
–2
–4
50
40
–6
5800MHz: GAIN
5800MHz: IP1dB
5800MHz: IIP2, I CHANNEL
5800MHz: IIP2, Q CHANNEL
30
–8
–10
–12
–14
–16
20
10
0
1
2
3
4
5.1
5.2
5.3
5.4
5.5
5.6
5.7
5.8
V
(V)
RF FREQUENCY (GHz)
ADJ
Figure 41. Conversion Gain, IP1dB, and IIP2 vs.
BIAS, fLO = 5800 MHz
Figure 44. RF Port Return Loss vs. RF Frequency Measured on
Characterization Board Through Johanson Technology 5400 Balun
R
Rev. 0 | Page 15 of 36
ADL5380
–0
–2
–4
–6
–8
–10
–12
–14
–16
5.1
5.2
5.3
5.4
5.5
5.6
5.7
5.8
5.9
6.0
LO FREQUENCY (GHz)
Figure 45. LO Port Return Loss vs. LO Frequency Measured on
Characterization Board Through Johanson Technology 5400 Balun
Rev. 0 | Page 16 of 36
ADL5380
DISTRIBUTIONS FOR fLO = 900 MHz
100
100
90
80
70
60
50
40
30
20
10
0
90
80
70
60
50
40
30
T
T
T
= –40°C
= +25°C
= +85°C
A
A
A
I CHANNEL
Q CHANNEL
T
T
T
= –40°C
= +25°C
= +85°C
A
A
A
20
10
0
28
29
30
31
32
33
34
14
0.3
45
50
55
60
65
70
75
80
85
12.5
1.0
INPUT IP3 (dBm)
INPUT IP2 (dBm)
Figure 49. IIP2 Distributions for I Channel and Q Channel
Figure 46. IIP3 Distributions
100
90
80
70
60
50
40
30
20
10
0
100
90
80
70
60
50
40
30
20
10
0
IP1dB
GAIN
T
T
T
= –40°C
= +25°C
= +85°C
T
T
T
= –40°C
= +25°C
= +85°C
A
A
A
A
A
A
9.5
10.0
10.5
11.0
11.5
12.0
4
5
6
7
8
9
10
11
12
13
NOISE FIGURE (dB)
GAIN (dB), IP1dB (dBm)
Figure 50. Noise Figure Distributions
Figure 47. Gain and IP1dB Distributions
100
90
80
70
60
50
40
30
20
10
0
100
90
80
70
60
50
40
30
20
10
0
T
T
T
= –40°C
= +25°C
= +85°C
A
A
A
T
T
T
= –40°C
= +25°C
= +85°C
A
A
A
–1.0 –0.8 –0.6 –0.4 –0.2
0
0.2
0.4
0.6
0.8
–0.3
–0.2
–0.1
0
0.1
0.2
QUADRATURE PHASE ERROR (Degrees)
GAIN MISMATCH (dB)
Figure 51. IQ Quadrature Phase Error Distributions
Figure 48. IQ Gain Mismatch Distributions
Rev. 0 | Page 17 of 36
ADL5380
DISTRIBUTIONS FOR fLO = 1900 MHz
100
90
80
70
60
50
40
30
20
10
0
100
T
T
T
= –40°C
= +25°C
= +85°C
A
A
A
90
80
70
60
50
40
30
I CHANNEL
Q CHANNEL
T
T
T
= –40°C
= +25°C
= +85°C
20
10
0
A
A
A
24
25
26
27
28
29
30
31
32
45
50
55
60
65
70
75
80
13.5
1.0
INPUT IP2 (dBm)
INPUT IP3 (dBm)
Figure 52. IIP3 Distributions
Figure 55. IIP2 Distributions for I Channel and Q Channel
100
90
80
70
60
50
40
30
20
10
0
100
90
80
70
60
50
40
30
20
10
0
T
T
T
= –40°C
= +25°C
= +85°C
A
A
A
IP1dB
GAIN
T
T
T
= –40°C
= +25°C
= +85°C
A
A
A
4
5
6
7
8
9
10
11
12
13
14
10.5
11.0
11.5
12.0
12.5
13.0
GAIN (dB), IP1dB (dBm)
NOISE FIGURE (dB)
Figure 53. Gain and IP1dB Distributions
Figure 56. Noise Figure Distributions
100
90
80
70
60
50
40
30
20
10
0
100
90
80
70
60
50
40
30
20
10
0
T
T
T
= –40°C
= +25°C
= +85°C
T
T
T
= –40°C
= +25°C
= +85°C
A
A
A
A
A
A
–1.0 –0.8 –0.6 –0.4 –0.2
0
0.2
0.4
0.6
0.8
–0.3
–0.2
–0.1
0
0.1
0.2
0.3
QUADRATURE PHASE ERROR (Degrees)
GAIN MISMATCH (dB)
Figure 57. IQ Quadrature Phase Error Distributions
Figure 54. IQ Gain Mismatch Distributions
Rev. 0 | Page 18 of 36
ADL5380
DISTRIBUTIONS FOR fLO = 2700 MHz
100
100
90
80
70
60
50
40
30
20
10
0
90
80
70
60
50
I CHANNEL
Q CHANNEL
T
T
T
= –40°C
= +25°C
= +85°C
A
A
A
40
30
20
10
0
T
T
T
= –40°C
= +25°C
= +85°C
A
A
A
18
20
22
24
26
28
30
32
34
36
35
40
45
50
55
60
65
70
75
14.0
2.0
INPUT IP3 (dBm)
INPUT IP2 (dBm)
Figure 58. IIP3 Distributions
Figure 61. IIP2 Distributions for I Channel and Q Channel
100
90
80
70
60
50
40
30
20
10
0
100
90
80
70
60
50
40
30
20
10
0
T
T
T
= –40°C
= +25°C
= +85°C
A
A
A
IP1dB
GAIN
T
T
T
= –40°C
= +25°C
= +85°C
A
A
A
4
5
6
7
8
9
10
11
12
13
14
10.5
11.0
11.5
12.0
12.5
13.0
13.5
GAIN (dB), IP1dB (dBm)
NOISE FIGURE (dB)
Figure 59. Gain and IP1dB Distributions
Figure 62. Noise Figure Distributions
100
90
80
70
60
50
40
30
20
10
0
100
90
80
70
60
50
40
30
20
10
0
T
T
T
= –40°C
= +25°C
= +85°C
A
A
A
T
T
T
= –40°C
= +25°C
= +85°C
A
A
A
–0.3
–0.2
–0.1
0
0.1
0.2
0.3
–2.0
–1.5
–1.0
–0.5
0
0.5
1.0
1.5
GAIN MISMATCH (dB)
QUADRATURE PHASE ERROR (Degrees)
Figure 60. IQ Gain Mismatch Distributions
Figure 63. IQ Quadrature Phase Error Distributions
Rev. 0 | Page 19 of 36
ADL5380
DISTRIBUTIONS FOR fLO = 3600 MHz
100
100
90
80
70
60
50
40
30
20
10
0
I CHANNEL
Q CHANNEL
T
T
T
= –40°C
= +25°C
= +85°C
90
80
70
60
50
40
30
20
10
0
A
A
A
T
T
T
= –40°C
= +25°C
= +85°C
A
A
A
15
17
19
21
23
25
27
29
31
33
35
40
45
50
55
60
65
70
16.0
2.5
INPUT IP2 (dBm)
INPUT IP3 (dBm)
Figure 64. IIP3 Distributions
Figure 67. IIP2 Distributions for I Channel and Q Channel
100
90
80
70
60
50
40
30
20
10
0
100
90
80
70
60
50
40
30
20
10
0
T
T
T
= –40°C
= +25°C
= +85°C
IP1dB
GAIN
A
A
A
T
T
T
= –40°C
= +25°C
= +85°C
A
A
A
4
5
6
7
8
9
10
11
12
13
14
12.5
13.0
13.5
14.0
14.5
15.0
15.5
GAIN (dB), IP1dB (dBm)
NOISE FIGURE (dB)
Figure 65. Gain and IP1dB Distributions
Figure 68. Noise Figure Distributions
100
90
80
70
60
50
40
30
20
10
0
100
90
80
70
60
50
40
30
20
10
0
T
T
T
= –40°C
= +25°C
= +85°C
A
A
A
T
T
T
= –40°C
= +25°C
= +85°C
A
A
A
–0.3
–0.2
–0.1
0
0.1
0.2
0.3
–0.5
0
0.5
1.0
1.5
2.0
GAIN MISMATCH (dB)
QUADRATURE PHASE ERROR (Degrees)
Figure 66. IQ Gain Mismatch Distributions
Figure 69. IQ Quadrature Phase Error Distributions
Rev. 0 | Page 20 of 36
ADL5380
DISTRIBUTIONS FOR fLO = 5800 MHz
100
100
90
80
70
60
50
40
30
20
10
0
T
T
T
= –40°C
= +25°C
= +85°C
90
80
70
60
50
40
30
20
10
0
I CHANNEL
Q CHANNEL
T
T
T
= –40°C
= +25°C
= +85°C
A
A
A
A
A
A
18
19
20
21
22
23
24
30
35
40
45
50
55
60
65
70
INPUT IP3 (dBm)
INPUT IP2 (dBm)
Figure 73. IIP2 Distributions for I Channel and Q Channel
Figure 70. IIP3 Distributions
100
90
80
70
60
50
40
30
20
10
0
100
T
T
T
= –40°C
= +25°C
= +85°C
A
A
A
90
80
70
60
50
40
30
20
10
0
T
T
T
= –40°C
= +25°C
= +85°C
A
A
A
IP1dB
GAIN
2
3
4
5
6
7
8
9
10
13.0 13.5 14.0 14.5 15.0 15.5 16.0 16.5 17.0 17.5 18.0
NOISE FIGURE (dB)
GAIN (dB), IP1dB (dBm)
Figure 74. Noise Figure Distributions
Figure 71. Gain and IP1dB Distributions
100
90
80
70
60
50
40
30
20
10
0
100
90
80
70
60
50
40
30
20
10
0
T
T
T
= –40°C
= +25°C
= +85°C
A
A
A
T
T
T
= –40°C
= +25°C
= +85°C
A
A
A
–3
–2
–1
0
1
2
3
–0.3
–0.2
–0.1
0
0.1
0.2
0.3
QUADRATURE PHASE ERROR (Degrees)
GAIN MISMATCH (dB)
Figure 75. IQ Quadrature Phase Error Distributions
Figure 72. IQ Gain Mismatch Distributions
Rev. 0 | Page 21 of 36
ADL5380
CIRCUIT DESCRIPTION
The ADL5380 can be divided into five sections: the local
oscillator (LO) interface, the RF voltage-to-current (V-to-I)
converter, the mixers, the differential emitter follower outputs,
and the bias circuit. A detailed block diagram of the device is
shown in Figure 76.
Table 4. ADJ Pin Resistor Values and Approximate ADJ Pin
Voltages
~ Baseband Common-
Mode Output (V)
RADJ
~VADJ (V)
200 Ω to VS
600 Ω to VS
1.54 kΩ to VS
3.8 kΩ to VS
10 kΩ to VS
Open
9 kΩ to GND
3.5 kΩ to GND
1.5 kΩ to GND
4.8
4.5
4
3.5
3
2.5
2
1.5
1
2.2
2.3
2.5
2.7
3
3.2
3.4
3.6
3.8
ENBL ADJ
ADL5380
IHI
BIAS
ILO
LOIP
RFIN
QUADRATURE
PHASE SPLITTER
V2I
RFIP
MIXERS
LOIN
QHI
The ADL5380 has two double-balanced mixers: one for the in-
phase channel (I channel) and one for the quadrature channel
(Q channel). These mixers are based on the Gilbert cell design
of four cross-connected transistors. The output currents from
the two mixers are summed together in the resistive loads that
then feed into the subsequent emitter follower buffers.
QLO
Figure 76. Block Diagram
EMITTER FOLLOWER BUFFERS
The LO interface generates two LO signals at 90° of phase
difference to drive two mixers in quadrature. RF signals are
converted into currents by the V-to-I converters that feed into
the two mixers. The differential I and Q outputs of the mixers
are buffered via emitter followers. Reference currents to each
section are generated by the bias circuit. A detailed description
of each section follows.
The output emitter followers drive the differential I and Q signals
off chip. The output impedance is set by on-chip 25 ꢀ series
resistors that yield a 50 ꢀ differential output impedance for
each baseband port. The fixed output impedance forms a
voltage divider with the load impedance that reduces the effective
gain. For example, a 500 ꢀ differential load has 1 dB lower
effective gain than a high (10 kꢀ) differential load impedance.
LO INTERFACE
BIAS CIRCUIT
The LO interface consists of a polyphase quadrature splitter
followed by a limiting amplifier. The LO input impedance is set
by the polyphase, which splits the LO signal into two differential
signals in quadrature. The LO input impedance is nominally
50 ꢀ. Each quadrature LO signal then passes through a limiting
amplifier that provides the mixer with a limited drive signal. For
optimal performance, the LO inputs must be driven differentially.
A band gap reference circuit generates the reference currents
used by different sections. The bias circuit can be enabled and
partially disabled using ENBL (Pin 7). If ENBL is grounded or
left open, the part is fully enabled. Pulling ENBL high shuts off
certain sections of the bias circuitry, reducing the standing
power to about half of its fully enabled consumption and
disabling the outputs.
V-TO-I CONVERTER
The differential RF input signal is applied to a V-to-I converter
that converts the differential input voltage to output currents.
The V-to-I converter provides a differential 50 ꢀ input impedance.
The V-to-I bias current can be adjusted up or down using the
ADJ pin (Pin 19). Adjusting the current up improves IIP3 and
IP1dB but degrades SSB NF. Adjusting the current down improves
SSB NF but degrades IIP3 and IP1dB. The current adjustment
can be made by connecting a resistor from the ADJ pin (Pin 19)
to VS to increase the bias current or to ground to decrease the
bias current. Table 4 approximately dictates the relationship
between the resistor used (RADJ), the resulting ADJ pin voltage,
and the resulting baseband common-mode output voltage.
Rev. 0 | Page 22 of 36
ADL5380
APPLICATIONS INFORMATION
BASIC CONNECTIONS
LOCAL OSCILLATOR (LO) INPUT
Figure 78 shows the basic connections schematic for the ADL5380.
For optimum performance, drive the LO port differentially
through a balun. The recommended balun for each performance
level includes the following:
POWER SUPPLY
The nominal voltage supply for the ADL5380 is 5 V and is
applied to the VCC1, VCC2, and VCC3 pins. Connect ground
to the GND1, GND2, GND3, and GND4 pins. Solder the exposed
paddle on the underside of the package to a low thermal and
electrical impedance ground plane. If the ground plane spans
multiple layers on the circuit board, these layers should be stitched
together with nine vias under the exposed paddle. The AN-772
Application Note discusses the thermal and electrical grounding
of the LFCSP in detail. Decouple each of the supply pins using
two capacitors; recommended capacitor values are 100 pF and 0.1 μF.
•
•
Up to 3 GHz is the Mini-Circuits TC1-1-13.
From 3 GHz to 4 GHz is the Johanson Technology
3600BL14M050.
From 4.9 GHz to 6 GHz is the Johanson Technology
5400BL15B050.
•
AC couple the LO inputs to the device with 100 pF capacitors.
The LO port is designed for a broadband 50 ꢀ match from
400 MHz to 6 GHz. The LO return loss can be seen in Figure 19.
Figure 77 shows the LO input configuration.
LO INPUT
9
LOIP
LOIN
100pF
100pF
BALUN
10
Figure 77. Differential LO Drive
The recommended LO drive level is between −6 dBm and +6 dBm.
The applied LO frequency range is between 400 MHz and 6 GHz.
RFIN
BALUN
100pF
100pF
RADJ
V
S
V
S
100pF
0.1µF
24
23
22
21
20
19
1
GND3 18
GND2 17
QHI 16
GND3
2 GND1
3 IHI
QHI
IHI
ADL5380
4 ILO
QLO 15
GND2 14
VCC2 13
ILO
QLO
5 GND1
6 VCC1
V
V
S
S
0.1µF
100pF
100pF
0.1µF
7
8
9
10
11
12
100pF
100pF
BALUN
LO_SE
Figure 78. Basic Connections Schematic
Rev. 0 | Page 23 of 36
ADL5380
RF INPUT
3
4
16
15
IHI
QHI
ADL5380
The RF inputs have a differential input impedance of approximately
50 ꢀ. For optimum performance, drive the RF port differentially
through a balun. The recommended balun for each performance
level includes the following:
ILO
QLO
Figure 81. Baseband Output Configuration
•
•
Up to 3 GHz is the Mini-Circuits TC1-1-13.
From 3 GHz to 4 GHz is the Johanson Technology
3600BL14M050.
From 4.9 GHz to 6 GHz is the Johanson Technology
5400BL15B050.
ERROR VECTOR MAGNITUDE (EVM) PERFORMANCE
EVM is a measure used to quantify the performance of a digital
radio transmitter or receiver. A signal received by a receiver has all
constellation points at their ideal locations; however, various
imperfections in the implementation (such as magnitude
•
imbalance, noise floor, and phase imbalance) cause the actual
constellation points to deviate from their ideal locations.
AC couple the RF inputs to the device with 100 pF capacitors.
Figure 79 shows the RF input configuration.
In general, a demodulator exhibits three distinct EVM
limitations vs. received input signal power. At strong signal
levels, the distortion components falling in-band due to non-
linearities in the device cause strong degradation to EVM
as signal levels increase. At medium signal levels, where the
demodulator behaves in a linear manner and the signal is well
above any notable noise contributions, the EVM has a tendency to
reach an optimum level determined dominantly by the quadrature
accuracy of the demodulator and the precision of the test equipment.
As signal levels decrease, such that noise is a major contribution,
the EVM performance vs. the signal level exhibits a decibel-for-
decibel degradation with decreasing signal level. At lower signal
levels, where noise proves to be the dominant limitation, the
decibel EVM proves to be directly proportional to the SNR.
21
RFIN
RFIP
100pF
100pF
BALUN
22
RF INPUT
Figure 79. RF Input
The differential RF port return loss is characterized, as shown
in Figure 80.
–8
–10
–12
–14
–16
–18
–20
–22
–24
–26
–28
–30
The ADL5380 shows excellent EVM performance for various
modulation schemes. Figure 82 shows the EVM performance of
the ADL5380 with a 16 QAM, 200 kHz low IF.
0
–5
–10
–15
–20
–25
–30
–35
–40
0
0.5 1.0 1.5 2.0 2.5 3.0 3.5 4.0 4.5 5.0 5.5 6.0
RF FREQUENCY (GHz)
Figure 80. Differential RF Port Return Loss
–45
–50
BASEBAND OUTPUTS
The baseband outputs QHI, QLO, IHI, and ILO are fixed
impedance ports. Each baseband pair has a 50 ꢀ differential
output impedance. The outputs can be presented with differential
loads as low as 200 ꢀ (with some degradation in gain) or high
impedance differential loads (500 ꢀ or greater impedance yields
the same excellent linearity) that is typical of an ADC. The TCM9-1
9:1 balun converts the differential IF output to a single-ended
output. When loaded with 50 ꢀ, this balun presents a 450 ꢀ
load to the device. The typical maximum linear voltage swing for
these outputs is 2 V p-p differential. The output 3 dB bandwidth
is 390 MHz. Figure 81 shows the baseband output configuration.
–90
–70
–50
–30
–10
10
RF INPUT POWER (dBm)
Figure 82. EVM, RF = 900 MHz, IF = 200 kHz vs.
RF Input Power for a 16 QAM 160ksym/s Signal
Rev. 0 | Page 24 of 36
ADL5380
Figure 83 shows the zero-IF EVM performance of a 10 MHz
IEEE 802.16e WiMAX signal through the ADL5380. The
differential dc offsets on the ADL5380 are in the order of a few
millivolts. However, ac coupling the baseband outputs with 10 μF
capacitors eliminates dc offsets and enhances EVM performance.
With a 10 MHz BW signal, 10 μF ac coupling capacitors with
the 500 ꢀ differential load results in a high-pass corner frequency
of ~64 Hz, which absorbs an insignificant amount of modulated
signal energy from the baseband signal. By using ac coupling
capacitors at the baseband outputs, the dc offset effects, which
can limit dynamic range at low input power levels, can be
eliminated.
Figure 84 exhibits multiple W-CDMA low-IF EVM performance
curves over a wide RF input power range into the ADL5380. In
the case of zero-IF, the noise contribution by the vector signal
analyzer becomes predominant at lower power levels, making it
difficult to measure SNR accurately.
–10
–15
–20
–25
–30
0
0Hz IF
–35
–10
–20
–30
2.5MHz LOW-IF 5MHz LOW-IF
–40
7.5MHz LOW-IF
–45
–80
–70
–60
–50
–40
–30
–20
–10
0
10
RF INPUT POWER (dBm)
Figure 84. EVM, RF = 1900 MHz, IF = 0 Hz, IF = 2.5 MHz, IF = 5 MHz, and IF =
7.5 MHz vs. RF Input Power for a W-CDMA Signal (AC-Coupled Baseband Outputs)
5.8GHz
3.5GHz
–40
LOW IF IMAGE REJECTION
–50
The image rejection ratio is the ratio of the intermediate frequency
(IF) signal level produced by the desired input frequency to that
produced by the image frequency. The image rejection ratio is
expressed in decibels. Appropriate image rejection is critical
because the image power can be much higher than that of the
desired signal, thereby plaguing the down-conversion process.
Figure 85 illustrates the image problem. If the upper sideband
(lower sideband) is the desired band, a 90° shift to the Q channel
(I channel) cancels the image at the lower sideband (upper sideband).
Phase and gain balance between I and Q channels are critical
for high levels of image rejection.
2.6GHz
–60
–75
–65
–55
–45
–35
–25
–15
–5
5
RF INPUT POWER (dBm)
Figure 83. EVM, RF = 2.6 GHz, RF = 3.5 GHz, and RF = 5.8 GHz, IF = 0 Hz vs.
RF Input Power for a 16 QAM 10 MHz Bandwidth Mobile WiMAX Signal
(AC-Coupled Baseband Outputs)
COSωLO
t
0°
ωIF
ωIF
0
0
+
ωIF
–
ωIF
0
+ωIF
–90°
+90°
ωLSB ωLO ωUSB
0°
+ωIF
–
ωIF
0
+ωIF
SINωLO
t
Figure 85. Illustration of the Image Problem
Rev. 0 | Page 25 of 36
ADL5380
Figure 86 and Figure 87 show the excellent image rejection
capabilities of the ADL5380 for low IF applications, such as
W-CDMA. The ADL5380 exhibits image rejection greater than
45 dB over a broad frequency range.
It is necessary to consider the overall source and load impedance
presented by the ADL5380 and ADC input when designing the
filter network. The differential baseband output impedance of
the ADL5380 is 50 ꢀ. The ADL5380 is designed to drive a high
impedance ADC input. It may be desirable to terminate the
ADC input down to lower impedance by using a terminating
resistor, such as 500 ꢀ. The terminating resistor helps to better
define the input impedance at the ADC input at the cost of a
slightly reduced gain (see the Circuit Description section for
details on the emitter-follower output loading effects).
60
50
2.5MHz LOW IF
5MHz LOW IF
40
7MHz LOW IF
30
The order and type of filter network depends on the desired high
frequency rejection required, pass-band ripple, and group delay.
Filter design tables provide outlines for various filter types and
orders, illustrating the normalized inductor and capacitor values
for a 1 Hz cutoff frequency and 1 ꢀ load. After scaling the
normalized prototype element values by the actual desired
cut-off frequency and load impedance, the series reactance
elements are halved to realize the final balanced filter network
component values.
20
10
0
400
800 1200 1600 2000 2400 2800 3200 3600 4000
RF FREQUENCY (MHz)
Figure 86. Low Band and Midband Image Rejection vs. RF Frequency for a
W-CDMA Signal, IF = 2.5 MHz, 5 MHz, and 7.5 MHz
As an example, a second-order Butterworth, low-pass filter design
is shown in Figure 88 where the differential load impedance is
500 ꢀ and the source impedance of the ADL5380 is 50 ꢀ. The
normalized series inductor value for the 10-to-1, load-to-source
impedance ratio is 0.074 H, and the normalized shunt capacitor
is 14.814 F. For a 10.9 MHz cutoff frequency, the single-ended
equivalent circuit consists of a 0.54 μH series inductor followed
by a 433 pF shunt capacitor.
60
50
40
2.5MHz LOW IF
5MHz LOW IF
7MHz LOW IF
30
20
10
0
The balanced configuration is realized as the 0.54 μH inductor
is split in half to realize the network shown in Figure 88.
R
= 50Ω
L
= 0.074H
S
N
NORMALIZED
SINGLE-ENDED
CONFIGURATION
V
C
14.814F
R = 500Ω
S
N
L
5000
5200
5400
5600
5800
6000
RF FREQUENCY (MHz)
R
R
S
L
fC = 1Hz
Figure 87. High Band Image Rejection vs. RF Frequency for a W-CDMA Signal,
IF = 2.5 MHz, 5 MHz, and 7.5 MHz
= 0.1
0.54µH
R
= 50Ω
S
EXAMPLE BASEBAND INTERFACE
DENORMALIZED
SINGLE-ENDED
EQUIVALENT
V
V
433pF
433pF
R = 500Ω
S
L
In most direct-conversion receiver designs, it is desirable to
select a wanted carrier within a specified band. The desired
channel can be demodulated by tuning the LO to the appropriate
carrier frequency. If the desired RF band contains multiple
carriers of interest, the adjacent carriers are also down converted to
a lower IF frequency. These adjacent carriers can be problematic if
they are large relative to the wanted carrier because they can
overdrive the baseband signal detection circuitry. As a result, it
is often necessary to insert a filter to provide sufficient rejection
of the adjacent carriers.
fC = 10.9MHz
R
2
S
= 25Ω
= 25Ω
0.27µH
R
2
L
= 250Ω
= 250Ω
BALANCED
CONFIGURATION
S
R
L
2
R
0.27µH
S
2
Figure 88. Second-Order Butterworth, Low-Pass Filter Design Example
Rev. 0 | Page 26 of 36
ADL5380
900
800
700
600
500
400
300
200
100
A complete design example is shown in Figure 91. A sixth-order
Butterworth differential filter having a 1.9 MHz corner frequency
interfaces the output of the ADL5380 to that of an ADC input.
The 500 ꢀ load resistor defines the input impedance of the
ADC. The filter adheres to typical direct conversion W-CDMA
applications where, 1.92 MHz away from the carrier IF frequency,
1 dB of rejection is desired, and, 2.7 MHz away from the carrier IF
frequency, 10 dB of rejection is desired.
Figure 89 and Figure 90 show the measured frequency response
and group delay of the filter.
10
0
0.2
0.4
0.6
0.8
1.0
1.2
1.4
1.6
1.8
5
0
FREQUENCY (MHz)
Figure 90. Sixth-Order Baseband Filter Group Delay
–5
–10
–15
–20
0
0.5
1.0
1.5
2.0
2.5
3.0
3.5
FREQUENCY (MHz)
Figure 89. Sixth-Order Baseband Filter Response
Rev. 0 | Page 27 of 36
ADL5380
RFIN
BALUN
100pF
100pF
V
V
S
S
100pF
0.1µF
24
23
22
21
20
19
1
GND3 18
GND3
2 GND1
3 IHI
GND2 17
QHI 16
ADL5380
4 ILO
QLO 15
GND2 14
VCC2 13
5 GND1
6 VCC1
V
V
S
S
0.1µF
100pF
100pF
0.1µF
7
8
9
10
11
12
100pF
100pF
BALUN
LO_SE
C
C
C
C
AC
AC
AC
AC
10µF
10µF
10µF
10µF
27µH
27µH
27µH
27µH
270pF
270pF
100pF
68pF
27µH
10µH
27µH
10µH
27µH
10µH
27µH
10µH
100pF
68pF
500Ω
500Ω
ADC INPUT
ADC INPUT
Figure 91. Sixth-Order Low-Pass Butterworth, Baseband Filter Schematic
Rev. 0 | Page 28 of 36
ADL5380
Figure 93 and Figure 94 illustrate the magnitude response and
group delay response of the fourth-order filter, respectively.
As the load impedance of the filter increases, the filter design
becomes more challenging in terms of meeting the required
rejection and pass band specifications. In the previous W-CDMA
example, the 500 ꢀ load impedance resulted in the design of a
sixth-order filter that has relatively large inductor values and small
capacitor values. If the load impedance is 200 ꢀ, the filter design
becomes much more manageable. Figure 92 shows a fourth-order
filter designed for a 10 MHz wide LTE signal. As shown in Figure 92,
the resultant inductor and capacitor values become much more
practical with a 200 ꢀ load.
5
0
–5
–10
–15
–20
–25
–30
–35
–40
2.2µH
1.5µH
0
5
10
15
20
25
30
35
40
FREQUENCY (MHz)
2.2µH
1.5µH
Figure 93. Fourth-Order Low-Pass LTE Filter Magnitude Response
Figure 92. Fourth-Order Low-Pass LTE Filter Schematic
60
50
40
30
20
10
0
0
5
10
15
20
25
30
35
40
FREQUENCY (MHz)
Figure 94. Fourth-Order Low-Pass LTE Filter Group Delay Response
Rev. 0 | Page 29 of 36
ADL5380
CHARACTERIZATION SETUPS
Figure 95 to Figure 97 show the general characterization bench
setups used extensively for the ADL5380. The setup shown in
Figure 97 was used to do the bulk of the testing and used sinusoidal
signals on both the LO and RF inputs. An automated Agilent
VEE program was used to control the equipment over the
IEEE bus. This setup was used to measure gain, IP1dB, IIP2,
IIP3, I/Q gain match, and quadrature error. The ADL5380
characterization board had a 9-to-1 impedance transformer on
each of the differential baseband ports to do the differential-to-
single-ended conversion, which presented a 450 ꢀ differential load
to each baseband port, when interfaced with 50 ꢀ test equipment.
The two setups shown in Figure 95 and Figure 96 were used
for making NF measurements. Figure 95 shows the setup for
measuring NF with no blocker signal applied while Figure 96
was used to measure NF in the presence of a blocker. For both
setups, the noise was measured at a baseband frequency of
10 MHz. For the case where a blocker was applied, the output
blocker was at a 15 MHz baseband frequency. Note that great
care must be taken when measuring NF in the presence of a
blocker. The RF blocker generator must be filtered to prevent
its noise (which increases with increasing generator output power)
from swamping the noise contribution of the ADL5380. At least
30 dB of attention at the RF and image frequencies is desired.
For example, assume a 915 MHz signal applied to the LO inputs of
the ADL5380. To obtain a 15 MHz output blocker signal, the RF
blocker generator is set to 930 MHz and the filters tuned such
that there is at least 30 dB of attenuation from the generator at
both the desired RF frequency (925 MHz) and the image RF
frequency (905 MHz). Finally, the blocker must be removed
from the output (by the 10 MHz low-pass filter) to prevent
the blocker from swamping the analyzer.
For all measurements of the ADL5380, the loss of the RF input
balun was de-embedded. Due to the wideband nature of the
ADL5380, three different board configurations had to be used to
characterize the product. For low band characterization (400 MHz
to 3 GHz), the Mini-Circuits TC1-1-13 balun was used on the
RF and LO inputs to create differential signals at the device pins.
For midband characterization (3 GHz to 4 GHz), the Johanson
Technology 3600BL14M050T was used, and for high band
characterization (5 GHz to 6 GHz), the Johanson Technology
5400BL15B050E balun was used.
SNS
CONTROL
AGILENT N8974A
NOISE FIGURE ANALYZER
OUTPUT
R1
50Ω
RF
Q
GND
ADL5380
CHAR BOARD
V
POS
I
LO
HP 6235A
POWER SUPPLY
INPUT
LOW-PASS
FILTER
AGILENT 8665B
SIGNAL GENERATOR
IEEE
PC CONTROLLER
Figure 95. General Noise Figure Measurement Setup
Rev. 0 | Page 30 of 36
ADL5380
BAND-PASS
TUNABLE FILTER
BAND-REJECT
TUNABLE FILTER
R&S SMT03
SIGNAL GENERATOR
R&S FSEA30
SPECTRUM ANALYZER
R1
50Ω
RF
Q
I
GND
ADL5380
LOW-PASS
FILTER
6dB PAD
CHAR BOARD
V
POS
LO
HP 6235A
POWER SUPPLY
BAND-PASS
CAVITY FILTER
HP 87405
LOW NOISE
PREAMP
AGILENT 8665B
SIGNAL GENERATOR
Figure 96. Measurement Setup for Noise Figure in the Presence of a Blocker
3dB PAD
RF
AMPLIFIER
IN
OUT
3dB PAD
RF
3dB PAD
VP GND
AGILENT
11636A
3dB PAD
R&S SMT06
RF
R&S SMT06
RF
Q
I
6dB PAD
GND
SWITCH
MATRIX
ADL5380
CHAR BOARD
V
POS
6dB PAD
LO
AGILENT E3631
POWER SUPPLY
RF
INPUT
AGILENT E8257D
SIGNAL GENERATOR
IEEE
IEEE
R&S FSEA30
SPECTRUM ANALYZER
HP 8508A
VECTOR VOLTMETER
PC CONTROLLER
Figure 97. General Characterization Setup
Rev. 0 | Page 31 of 36
ADL5380
EVALUATION BOARD
The ADL5380 evaluation board is available. There are two
versions of the board, optimized for performance for separate
frequency ranges. For operation <3 GHz, an FR4 material-based
board with the TC1-1-13 balun footprint is available. For operation
between 3 GHz to 6 GHz, a Rogers® material-based RO3003 board
with the Johanson Technology 3600BL14M050 balun (optimal
for operation between 3 GHz and 4 GHz) footprint is available.
The Johanson Technology 5400BL15K050 shares the same
footprint and can be used for operation between 4900 MHz to
5800 MHz.
The board can be used for single-ended or differential baseband
analysis. The default configuration of the board is for single-ended
baseband analysis.
RFx
T3x
C5x
C12x
R19x
R23x
V
V
POS
POS
24
23
22
21
20
19
C8x
C11x
1
2
3
4
5
6
GND3 18
GND2 17
GND3
GND1
IHI
R5x
R3x
QPx
QNx
IPx
INx
R16x
R14x
R18x
T2x
R17x
T4x
16
QHI
R6x
ADL5380
R7x
C16x
R15x
C15x
15
QLO
ILO
R13x
14
GND1
VCC1
GND2
R4x
V
R2x
POS
R10x
R12x
13
VCC2
V
POS
C9x
C6x
C7x
C10x
7
8
9
10
11
12
R9x
R1x
R11x
V
C2x
C3x
POS
C4x
C1x
P1x
T1x
V
POS
LONx
LOPx
LO_SE
NOTES
1. X = B, FOR LOW FREQUENCY OPERATION UP TO 3GHz, TC1-1-13 BALUN ON RF AND LO PORTS.
X = A, FOR FREQUENCY OPERATION FROM 3GHz TO 4GHz, JOHANSON TECHNOLOGY 3600BL14M050 BALUN ON RF AND LO PORTS.
2. FOR OPERATION BETWEEN 4.9GHZ TO 6GHZ, THE JOHANSON TECHNOLOGY 5400BL15K050 BALUN, WHICH SHARES A SIMILAR
FOOTPRINT AS THE 4GHZ BALUN, CAN BE USED.
Figure 98. Evaluation Board Schematic
Rev. 0 | Page 32 of 36
ADL5380
Table 5. Evaluation Board Configuration Options
Component Description
Default Condition
VPOSx, GNDx Power Supply and Ground Vector Pins.
Not applicable
R10x, R12x,
R19x
Power Supply Decoupling. Shorts or power supply decoupling resistors.
R10x, R12x, R19x = 0 Ω (0603)
C6x to C11x
The capacitors provide the required dc coupling up to 6 GHz.
Device Enable. When connected to VS, the device is active.
C6x, C7x, C8x = 100 pF (0402),
C9x, C10x, C11x = 0.1 μF (0603)
P1x, R11x,
R9x, R1x
P1x, R9x = DNI, R1x = DNI,
R11x = 0 Ω
R23x
Adjust Pin. The resistor value here sets the bias voltage at this pin and optimizes
third-order distortion.
R23B = 1.5 kΩ (0603),
R23A = 200 Ω (0603)
C1x to C5x,
C12x
AC Coupling Capacitors. These capacitors provide the required ac coupling
from 400 MHz to 4 GHz.
C1x, C4x = DNI,
C2x, C3x, C5x, C12x = 100 pF (0402)
R2x to R7x,
Single-Ended Baseband Output Path. This is the default configuration of the
R2x to R7x = open,
R13x to R18x = 0 Ω (0402)
R13x to R18x evaluation board. R13x to R18x are populated for appropriate balun interface.
R2x to R5x are not populated. Baseband outputs are taken from QHI and IHI. The
user can reconfigure the board to use full differential baseband outputs. R2x to R5x
provide a means to bypass the 9:1 TCM9-1 transformer to allow for differential base-
band outputs. Access the differential baseband signals by populating R2x to R5x
with 0 Ω and not populating R13x to R18x. This way the transformer does not need
to be removed. The baseband outputs are taken from the SMAs of QHI, QLO, IHI,
and ILO. R6x and R7x are provisions for applying a specific differential load across
the baseband outputs
T2x, T4x
IF Output Interface. TCM9-1 converts a differential high impedance IF output to
a single-ended output. When loaded with 50 Ω, this balun presents a 450 Ω load
to the device. The center tap can be decoupled through a capacitor to ground.
T2x, T4x = TCM9-1, 9:1 (Mini-Circuits)
C15x, C16x = 0.1 μF (0402)
C15x, C16x
T1x
Decoupling Capacitors. C15x and C16x are the decoupling capacitors used to reject
noise on the center tap of the TCM9-1.
LO Input Interface. A 1:1 RF balun that converts the single-ended RF input to
differential signal is used.
T1B = TC1-1-13, 1:1 (Mini-Circuits)
for operation <3 GHz,
T1A = Johanson Technology
3600BL14M050 for operation from
3 GHz to 4 GHz, Johanson Technology
5400BL15K050 for operation from
4900 MHz to 5800 MHz
T3x
RF Input Interface. A 1:1 RF balun that converts the single-ended RF input to
differential signal is used.
T3B = TC1-1-13, 1:1 (Mini-Circuits)
for operation <3 GHz,
T3A = Johanson Technology
3600BL14M050 for operation from
3 GHz to 4 GHz, Johanson Technology
5400BL15K050 for operation from
4900 MHz to 5800 MHz
Rev. 0 | Page 33 of 36
ADL5380
Figure 99. Low Band Evaluation Board Top Layer
Figure 101. Low Band Evaluation Board Bottom Layer
Figure 100. Midband/High Band Evaluation Board Top Layer Silkscreen
Figure 102. Midband/High Band Evaluation Board Bottom Layer Silkscreen
12 mil.
THERMAL GROUNDING AND EVALUATION
BOARD LAYOUT
23 mil.
25 mil.
The package for the ADL5380 features an exposed paddle on the
underside that should be well soldered to a low thermal and
electrical impedance ground plane. This paddle is typically
soldered to an exposed opening in the solder mask on the
evaluation board. Figure 103 illustrates the dimensions used in
the layout of the ADL5380 footprint on the ADL5380 evaluation
board (1 mil = 0.0254 mm).
82 mil.
Notice the use of nine via holes on the exposed paddle. These
ground vias should be connected to all other ground layers on
the evaluation board to maximize heat dissipation from the
device package.
12 mil.
19.7 mil.
98.4 mil.
133.8 mil.
Figure 103. Dimensions for Evaluation Board Layout for the ADL5380 Package
Under these conditions, the thermal impedance of the ADL5380
was measured to be approximately 30°C/W in still air.
Rev. 0 | Page 34 of 36
ADL5380
OUTLINE DIMENSIONS
0.60 MAX
4.00
BSC SQ
0.60 MAX
PIN 1
INDICATOR
1
24
19
18
0.50
BSC
PIN 1
INDICATOR
2.65
2.50 SQ
2.35
TOP
VIEW
3.75
BSC SQ
EXPOSED
PA D
(BOTTOMVIEW)
0.50
0.40
0.30
6
13
12
7
0.23 MIN
0.80 MAX
0.65 TYP
2.50 REF
1.00
0.85
0.80
12° MAX
0.05 MAX
0.02 NOM
FOR PROPER CONNECTION OF
THE EXPOSED PAD, REFER TO
THE PIN CONFIGURATION AND
FUNCTION DESCRIPTIONS
0.30
0.23
0.18
COPLANARITY
0.08
0.20 REF
SEATING
PLANE
SECTION OF THIS DATA SHEET.
COMPLIANT TO JEDEC STANDARDS MO-220-VGGD-8
Figure 104. 24-Lead Lead Frame Chip Scale Package [LFCSP_VQ]
4 mm × 4 mm Body, Very Thin Quad
(CP-24-3)
Dimensions shown in millimeters
ORDERING GUIDE
Package
Option
Model
Temperature Range
–40°C to +85°C
–40°C to +85°C
Package Description
Ordering Quantity
ADL5380ACPZ-R71
ADL5380ACPZ-WP1
ADL5380-29A-EVALZ1
ADL5380-30A-EVALZ1
24-Lead LFCSP_VQ
24-Lead LFCSP_VQ
Mid Band (3 GHz to 4 GHz) Evaluation Board
Low Band (400 MHz to 3 GHz) Evaluation Board
CP-24-3
CP-24-3
1,500, 7”Tape and Reel
64, Waffle Pack
1
1
1 Z = RoHS Compliant Part.
Rev. 0 | Page 35 of 36
ADL5380
NOTES
©2009 Analog Devices, Inc. All rights reserved. Trademarks and
registered trademarks are the property of their respective owners.
D07585-0-7/09(0)
Rev. 0 | Page 36 of 36
相关型号：
ADL5386ACPZ-R2
SPECIALTY TELECOM CIRCUIT, QCC40, 6 X 6 MM, ROHS COMPLIANT, MO-220-VJJD-2, LFCSP-40
ADI
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