ADL5566-EVALZ [ADI]
4.5 GHz Ultrahigh Dynamic Range, Dual Differential Amplifier;型号: | ADL5566-EVALZ |
厂家: | ADI |
描述: | 4.5 GHz Ultrahigh Dynamic Range, Dual Differential Amplifier |
文件: | 总24页 (文件大小:885K) |
中文: | 中文翻译 | 下载: | 下载PDF数据表文档文件 |
4.5 GHz Ultrahigh Dynamic Range,
Dual Differential Amplifier
Data Sheet
ADL5566
FEATURES
FUNCTIONAL BLOCK DIAGRAM
VCC1/VCC2
ENBL1
−3 dB bandwidth of 4.5 GHz (AV = 16 dB)
Fixed 16 dB gain
Channel-to-channel gain error: 0.1 dB at 100 MHz
Channel-to-channel phase error: 0.06° at 100 MHz
Differential or single-ended input to differential output
I/O dc-coupled or ac-coupled
Low noise input stage: 1.3 nV/√Hz RTI at AV = 16 dB
Low broadband distortion (AV = 16 dB), supply = 5 V
10 MHz: −103 dBc (HD2), −107 dBc (HD3)
100 MHz: −95 dBc (HD2), −100 dBc (HD3)
200 MHz: −94.5 dBc (HD2), −87 dBc (HD3)
500 MHz: −83 dBc (HD2), −64 dBc (HD3)
IMD3 of −95 dBc at 200 MHz center
R
F
VON1
R
R
G
VIP1
VIN1
VCOM1
G
VOP1
R
R
F
Maintains low single-ended distortion performance out to
500 MHz
F
Slew rate: 16 V/ns
VON2
Maintains low distortion down to 1.2 V VCOM
Fixed 16 dB gain can be reduced by adding external resistors
Fast settling and overdrive recovery of 2.5 ns
Single-supply operation: 2.8 V to 5.2 V
Power-down
R
R
G
VIP2
VIN2
VCOM2
G
VOP2
Low dc power consumption, 462 mW at 3.3 V supply
R
APPLICATIONS
F
Differential ADC drivers
Single-ended to differential conversion
RF/IF gain blocks
ADL5566
GND
ENBL2
Figure 1.
SAW filter interfacing
GENERAL DESCRIPTION
The ADL5566 is a high performance, dual differential amplifier
optimized for IF and dc applications. The amplifier offers low
noise of 1.3 nV/√Hz and excellent distortion performance over
a wide frequency range, making it an ideal driver for high speed
16-bit analog-to-digital converters (ADCs). The ADL5566 is
ideally suited for use in high performance, zero IF/complex
IF receiver designs. In addition, this device has excellent low
distortion for single-ended input drive applications.
The quiescent current of the ADL5566, using a 3.3 V supply, is
typically 70 mA per amplifier. When disabled, it consumes less
than 3.5 mA per amplifier and has −25 dB of input to output
isolation at 100 MHz.
The device is optimized for wideband, low distortion, and noise
performance, giving it unprecedented performance for overall
spurious-free dynamic range (SFDR). These attributes, together
with the adjustable gain capability, make this device the amplifier of
choice for driving a wide variety of ADCs, mixers, pin diode
attenuators, SAW filters, and multi-element discrete devices.
The ADL5566 provides a gain of 16 dB. For the single-ended input
configuration, the gain is reduced to 14 dB. Using two external
series resistors for each amplifier expands the gain flexibility of
the amplifier and allows for any gain selection from 0 dB to 16 dB
for a differential input and 0 dB to 14 dB for a single-ended input.
In addition, this device maintains low distortion down to output
(VOCM) levels of 1.2 V providing an added capability for driving
CMOS ADCs at ac levels up to 2 V p-p.
Fabricated on an Analog Devices, Inc., high speed SiGe process, the
ADL5566 is supplied in a compact 4 mm × 4 mm, 24-lead LFCSP
package and operates over the −40°C to +85°C temperature range.
Rev. C
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Tel: 781.329.4700 ©2012–2019 Analog Devices, Inc. All rights reserved.
Technical Support
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ADL5566
Data Sheet
TABLE OF CONTENTS
Features .............................................................................................. 1
Applications Information.............................................................. 15
Basic Connections...................................................................... 15
Input and Output Interfacing ................................................... 16
Gain Adjustment and Interfacing ............................................ 16
ADC Interfacing......................................................................... 18
DC-Coupled Receiver Application.......................................... 18
Layout Considerations............................................................... 19
Soldering Information and Recommended Land Pattern.... 21
Evaluation Board........................................................................ 21
Outline Dimensions....................................................................... 24
Ordering Guide .......................................................................... 24
Applications....................................................................................... 1
Functional Block Diagram .............................................................. 1
General Description......................................................................... 1
Revision History ............................................................................... 2
Specifications..................................................................................... 3
Absolute Maximum Ratings............................................................ 6
Thermal Resistance ...................................................................... 6
ESD Caution.................................................................................. 6
Pin Configuration and Function Descriptions............................. 7
Typical Performance Characteristics ............................................. 8
Circuit Description......................................................................... 14
REVISION HISTORY
8/2019—Rev. B to Rev. C
12/2013—Rev. 0 to Rev. A
Changes to Figure 36...................................................................... 15
Changes to Figure 48...................................................................... 19
Updated Outline Dimensions....................................................... 24
Changes to Ordering Guide .......................................................... 24
Changes to ENBL1/ENBL2 Threshold Parameter, Table 1..........3
Change to Table 2 ..............................................................................6
11/2012—Revision 0: Initial Version
4/2019—Rev. A to Rev. B
Changes to Figure 26...................................................................... 11
Updated Outline Dimensions....................................................... 24
Rev. C | Page 2 of 24
Data Sheet
ADL5566
SPECIFICATIONS
VS = 3.3 V, VCM = 1.65 V, VS = 5 V, VCM = 2.5 V, RL = 200 Ω differential, AV = 16 dB, CL = 1 pF differential, f = 100 MHz, TA = 25°C,
parameters specified as ac-coupled differential input and differential output, unless otherwise noted.
Table 1.
Test Conditions/
Comments
3.3 V
Typ
5 V
Parameter
Min
Max Min
Typ
Max Unit
DYNAMIC PERFORMANCE
−3 dB Bandwidth
Bandwidth 0.1 dB Flatness
Gain Accuracy
AV = 16 dB, VOUT ≤ 0.5 V p-p
VOUT ≤ 1.0 V p-p
4500
500
1
4500
500
1
MHz
MHz
dB
Gain Error
≤1000 MHz, Channel A to
Channel B
≤0.02
≤0.02
dB
Phase Error
≤1000 MHz, Channel A to
Channel B
≤0.5
≤0.5
Degrees
Gain Supply Sensitivity
Gain Temperature Sensitivity
Slew Rate
VS 5%
−40°C to +85°C
Rise, AV = 16 dB, RL = 200 Ω,
VOUT = 2 V step
3.4
0.5
16
5.6
0.5
18
mdB/V
mdB/°C
V/ns
Fall, AV = 16 dB, RL = 200 Ω,
18
20
V/ns
VOUT = 2 V step
Settling Time
Overdrive Recovery Time
2 V step to 1%
VIN = 4 V to 0 V step,
890
2.5
750
2.5
ps
ns
VOUT
≤ 10 mV
Reverse Isolation (S12)
Channel Isolation
75
82.5
75
82.5
dB
dB
Channel A to Channel B
AV = 16 dB
INPUT/OUTPUT CHARACTERISTICS
Input Common-Mode Range
Input Resistance (Differential)
Input Resistance (Single-Ended)
Input Capacitance (Single-Ended)
Input Bias Current
1.2
1.8
1.3
3.5
V
Ω
Ω
pF
AV = 16 dB
AV = 14 dB
160
150
1.1
5
160
150
1.1
5
µA
CMRR
44
44
dB
Output Common-Mode Range
Output Common-Mode Offset
Output Common-Mode Drift
Output Differential Offset Voltage
Output Differential Offset Drift
Output Resistance (Differential)
Maximum Output Voltage Swing
POWER INTERFACE
1.25
−100
1.8
+20
1.25
−100
3
+20
V
Referenced to VCC/2
−40°C to +85°C
mV
mV/°C
mV
mV/°C
Ω
2
3.5
−20
+20
−20
+20
−40°C to +85°C
1.1
11
3.4
1.7
11
5
1 dB compressed
V p-p
Supply Voltage
ENBL1/ENBL2 Threshold
2.8
3.3
5.2
0.5
2.8
1.5
5
5.2
0.6
V
V
V
nA
µA
mA
mA
Device disabled, ENBL low
Device enabled, ENBL high 1.5
ENBL high
ENBL1/ENBL2 Input Bias Current
Quiescent Current
500
−165
140
7
500
−165
160
9
ENBL low
ENBL high
ENBL low
150
175
Rev. C | Page 3 of 24
ADL5566
Data Sheet
Test Conditions/
Comments
3.3 V
Typ
5 V
Parameter
Min
Max Min
Typ
Max Unit
NOISE/HARMONIC PERFORMANCE
10 MHz
Second/Third Harmonic
Distortion (HD2/HD3)
Output IP3/Third-Order
Intermodulation
AV = 16 dB, RL = 200 Ω,
−99.1/−111
−103.1/−107.3
+49.4/−101.8
dBc
V
OUT = 2 V p-p
AV = 16 dB, RL = 200 Ω,
OUT = 2 V p-p composite
+50.2/−103.3
dBm/dBc
V
Distortion (OIP3/IMD3)
(2 MHz spacing)
Output IP2 Second-Order
Intermodulation
AV = 16 dB, RL = 200 Ω,
dBm/dBc
+90.8/−92.1
+91.2/−92.5
V
OUT = 2 V p-p composite
Distortion (OIP2/IMD2)
(2 MHz spacing)
1 dB Compression Point, RTO
(OP1dB)
Noise Spectral Density,
RTI (NSD)
Noise Figure (NF)
100 MHz
AV = 16 dB
14
17.7
1.32
6.66
dBm
nV/√Hz
dB
AV = 16 dB
AV = 16 dB
1.28
6.47
Second/Third Harmonic
Distortion (HD2/HD3)
Output IP3/Third-Order
Intermodulation
AV = 16 dB, RL = 200 Ω,
−89/−92.1
−94.7/−100
dBc
V
OUT = 2 V p-p
AV = 16 dB, RL = 200 Ω,
OUT = 2 V p-p composite
+49.4/−101.9
+50.9/−104.7
dBm/dBc
V
Distortion (OIP3/IMD3)
(2 MHz spacing)
Output IP2 Second-Order
Intermodulation
AV = 16 dB, RL = 200 Ω,
+96.9/−98.2
+98.9/−100.2
dBm/dBc
V
OUT = 2 V p-p composite
Distortion (OIP2/IMD2)
(2 MHz spacing)
1 dB Compression Point, RTO
(OP1dB)
Noise Spectral Density,
RTI (NSD)
Noise Figure (NF)
200 MHz
AV = 16 dB
14.2
1.26
6.36
17.8
1.3
dBm
nV/√Hz
dB
AV = 16 dB
AV = 16 dB
6.58
Second/Third Harmonic
Distortion (HD2/HD3)
Output IP3/Third-Order
Intermodulation
AV = 16 dB, RL = 200 Ω,
−92.7/−80.2
+45.9/−94.7
−94.5/−87.2
+46/−95
dBc
V
OUT = 2 V p-p
AV = 16 dB, RL = 200 Ω,
OUT = 2 V p-p composite
dBm/dBc
V
Distortion (OIP3/IMD3)
(2 MHz spacing)
Output IP2 Second-Order
Intermodulation
AV = 16 dB, RL = 200 Ω,
+80.4/−81.7
+82.6/−83.9
dBm/dBc
V
OUT = 2 V p-p composite
Distortion (OIP2/IMD2)
(2 MHz spacing)
1 dB Compression Point, RTO
(OP1dB)
Noise Spectral Density,
RTI (NSD)
Noise Figure (NF)
500 MHz
AV = 16 dB
14.1
1.25
6.31
17.7
1.28
6.48
dBm
nV/√Hz
dB
AV = 16 dB
AV = 16 dB
Second/Third Harmonic
Distortion (HD2/HD3)
Output IP3/Third-Order
Intermodulation
AV = 16 dB, RL = 200 Ω,
−82.6/−60.5
+30.7/−64.7
−82.8/−64.2
+32.4/−67.8
dBc
V
OUT = 2 V p-p
AV = 16 dB, RL = 200 Ω,
OUT = 2 V p-p composite
dBm/dBc
V
Distortion (OIP3/IMD3)
(2 MHz spacing)
Output IP2 Second-Order
Intermodulation
AV = 16 dB, RL = 200 Ω,
+74.2/−75.5
+75.8/−77.1
dBm/dBc
V
OUT = 2 V p-p composite
Distortion (OIP2/IMD2)
(2 MHz spacing)
Noise Spectral Density,
RTI (NSD)
Noise Figure (NF)
AV = 16 dB
1.32
6.64
1.35
6.83
nV/√Hz
dB
AV = 16 dB
Rev. C | Page 4 of 24
Data Sheet
ADL5566
Test Conditions/
Comments
3.3 V
Typ
5 V
Parameter
Min
Max Min
Typ
Max Unit
1000 MHz
Second/Third Harmonic
Distortion (HD2/HD3)
Output IP3/Third-Order
Intermodulation
AV = 16 dB, RL = 200 Ω,
−57.6/−43
−57.1/−45.9
+24.8/−52.6
dBc
V
OUT = 2 V p-p
AV = 16 dB, RL = 200 Ω,
OUT = 2 V p-p composite
+23.2/−49.4
dBm/dBc
V
Distortion (OIP3/IMD3)
(2 MHz spacing)
Output IP2 Second-Order
Intermodulation
AV = 16 dB, RL = 200 Ω,
+56.1/−57.4
+55.9/−57.2
dBm/dBc
V
OUT = 2 V p-p composite
Distortion (OIP2/IMD2)
(2 MHz spacing)
Noise Spectral Density,
RTI (NSD)
Noise Figure (NF)
AV = 16 dB
1.93
9.45
1.99
9.66
nV/√Hz
dB
AV = 16 dB
Rev. C | Page 5 of 24
ADL5566
Data Sheet
ABSOLUTE MAXIMUM RATINGS
Table 2.
THERMAL RESISTANCE
Table 3 lists the junction to air thermal resistance (θJA) and the
junction to paddle thermal resistance (θJC) for the ADL5566.
Parameter
Rating
Output Voltage Swing × Bandwidth Product 2300 V p-p MHz
Supply Voltage, VCC
VIPx, VINx
IOUT Maximum
Internal Power Dissipation
Maximum Junction Temperature
Operating Temperature Range
Storage Temperature Range
5.25 V
VCC + 0.5 V
30 mꢀ
900 mW
135°C
Table 3. Thermal Resistance
Package Type
1
2
θJA
34.0
θJC
1.8
Unit
24-Lead LFCSP
°C/W
1 Measured on ꢀnalog Devices evaluation board. For more information about
board layout, see the Soldering Information and Recommended Land Pattern
section.
−40°C to +105°C
−65°C to +150°C
2 Based on simulation with JEDEC standard JESD51.
ESD CAUTION
Stresses at or above those listed under Absolute Maximum
Ratings may cause permanent damage to the product. This is a
stress rating only; functional operation of the product at these
or any other conditions above those indicated in the operational
section of this specification is not implied. Operation beyond
the maximum operating conditions for extended periods may
affect product reliability.
Rev. C | Page 6 of 24
Data Sheet
ADL5566
PIN CONFIGURATION AND FUNCTION DESCRIPTIONS
1
2
3
4
5
6
18
VON1
VIN1
VIP1
NC
17 VOP1
16
NC
ADL5566
TOP VIEW
15
NC
NC
VIP2
VIN2
14
VOP2
13 VON2
1. NC = NO CONNECT. DO NOT CONNECT TO THIS PIN.
2. THE EXPOSED PADDLE IS INTERNALLY CONNECTED TO
GND AND MUST BE SOLDERED TO A LOW IMPEDANCE
GROUND PLANE.
Figure 2. Pin Configuration
Table 4. Pin Function Descriptions
Pin No.
Mnemonic Description
1
2
VIN1
VIP1
NC
Balanced Differential Input for Amplifier 1. Biased to VCC/2, typically ac-coupled. Input for AV = 16 dB.
Balanced Differential Input for Amplifier 1. Biased to VCC/2, typically ac-coupled. Input for AV = 16 dB.
No Connect. Do not connect to this pin. Solder to ground.
3, 4, 7, 8, 12, 15,
16, 19, 23, 24
5
6
9
10
VIP2
VIN2
ENBL2
VCOM2
Balanced Differential Input for Amplifier 2. Biased to VCC/2, typically ac-coupled. Input for AV = 16 dB.
Balanced Differential Input for Amplifier 2. Biased to VCC/2, typically ac-coupled. Input for AV = 16 dB.
Enable for Amplifier 2. Apply positive voltage (1.3 V < ENBL2 < VCC2) to activate device.
Common-Mode Voltage. A voltage applied to this pin sets the common-mode voltage of the inputs and
outputs of Amplifier 2. If left open, VCOM2 = VCC/2. Typically, it is decoupled to ground with a 0.1 µF
capacitor.
11
13
14
17
18
20
21
VCC2
VON2
VOP2
VOP1
VON1
VCC1
VCOM1
Positive Supply for Amplifier 2.
Balanced Differential Output for Amplifier 2. Biased to VCC/2, typically ac-coupled.
Balanced Differential Output for Amplifier 2. Biased to VCC/2, typically ac-coupled.
Balanced Differential Output for Amplifier 1. Biased to VCC/2, typically ac-coupled.
Balanced Differential Output for Amplifier 1. Biased to VCC/2, typically ac-coupled.
Positive Supply for Amplifier 1.
Common-Mode Voltage. A voltage applied to this pin sets the common-mode voltage of the inputs and
outputs of Amplifier 1. If left open, VCOM1 = VCC/2. Typically, it is decoupled to ground with a 0.1 µF
capacitor.
22
ENBL1
EP
Enable for Amplifier 1. Apply positive voltage (1.3 V < ENBL1 < VCC1) to activate device.
The exposed paddle is internally connected to GND and must be soldered to a low impedance ground plane.
Rev. C | Page 7 of 24
ADL5566
Data Sheet
TYPICAL PERFORMANCE CHARACTERISTICS
VS = 3.3 V, VCM = 1.65 V, RL = 200 Ω differential, AV = 16 dB, CL = 1 pF differential, f = 100 MHz, TA = 25°C, parameters specified as
ac-coupled differential input and differential output, unless otherwise noted.
25
20
15
10
5
0.7
0.6
0.5
0.4
0.3
0.2
0.1
0
0.07
0.06
0.05
0.04
0.03
0.02
0.01
0
3.3V, 25°C
5V, 25°C
SDD21 PHASE
SDD21 MAG
0
–5
–10
–15
10M
100M
FREQUENCY (Hz)
1G
10
100
1000
FREQUENCY (MHz)
Figure 3. Gain vs. Frequency Response for 200 Ω Differential Load,
POS = 3.3 V and VPOS = 5 V, 25°C
Figure 6. Channel-to-Channel Gain Error and Phase Error vs. Frequency
V
25
20
15
10
5
25
3.3V, –40°C
3.3V, +25°C
3.3V, +85°C
3.3V, +105°C
20
15
10
0
5V, +25°C
5V, –40°C
5V, +85°C
5V, +105°C
3.3V, +25°C
3.3V, –40°C
3.3V, +85°C
3.3V, +105°C
–5
–10
–15
5
0
10M
100M
FREQUENCY (Hz)
1G
0
50
100
150
200
250
FREQUENCY (MHz)
Figure 4. Gain vs. Frequency Response for 200 Ω Differential Load,
Four Temperatures, VPOS = 3.3 V
Figure 7. OP1dB vs. Frequency for 200 Ω Differential Load, Four
Temperatures, VPOS = 3.3 V, VPOS = 5 V
25
10.0
5V, –40°C
3.3V SUPPLY
5V SUPPLY
5V, +25°C
9.5
9.0
8.5
8.0
7.5
7.0
6.5
6.0
5.5
5.0
4.5
4.0
3.5
3.0
5V, +85°C
5V, +105°C
20
15
10
5
0
–5
–10
–15
10M
100M
FREQUENCY (Hz)
1G
10M
100M
1G
FREQUENCY (Hz)
Figure 5. Gain vs. Frequency Response for 200 Ω Differential Load,
Four Temperatures, VPOS = 5 V
Figure 8. Noise Figure vs. Frequency at VPOS = 3.3 V, VPOS = 5 V, 25°C
Rev. C | Page 8 of 24
Data Sheet
ADL5566
3.00
60
50
40
30
20
10
0
3.3V SUPPLY
5V SUPPLY
2.75
2.50
2.25
2.00
1.75
1.50
1.25
1.00
0.75
0.50
0.25
0
OIP3, 5V, 25°C
OIP3, 3.3V, 25°C
10M
100M
1G
–6 –5 –4 –3 –2 –1
0
1
2
3
4
5
6
7
8
9
10
FREQUENCY (Hz)
P
/TONE (dBm)
OUT
Figure 9. Noise Spectral Density vs. Frequency at VPOS = 3.3 V and VPOS = 5 V
Figure 12. OIP3 vs. Output Power (POUT) per Tone, Frequency 200 MHz,
POS = 3.3 V and VPOS = 5 V
V
60
0
IMD3, 3.3V, +25°C, 2V p-p
IMD3, 5V, +25°C, 2V p-p
IMD3, 3.3V, +85°C, 2V p-p
IMD3,5V, +85°C, 2V p-p
IMD3, 3.3V, –40°C, 2V p-p
IMD3, 5V, –40°C, 2V p-p
IMD3, 3.3V, +105°C, 2V p-p
IMD3, 5V, +105°C, 2V p-p
IMD3, 3.3V, +25°C, 1V p-p
IMD3, 5V, +25°C, 1V p-p
IMD3, 3.3V, +85°C, 1V p-p
IMD3, 5V, +85°C, 1V p-p
IMD3, 3.3V, –40°C, 1V p-p
IMD3, 5V, –40°C, 1V p-p
IMD3, 3.3V, +105°C, 1V p-p
IMD3, 5V, +105°C, 1V p-p
OIP3, 3.3V, 25°C, 2V p-p
OIP3, 5V, 25°C, 2V p-p
OIP3, 3.3V, 25°C, 1V p-p
50
–20
OIP3, 5V, 25°C, 1V p-p
40
30
20
10
0
–40
–60
–80
–100
–120
0
100 200 300 400 500 600 700 800 900 1000
FREQUENCY (MHz)
0
100 200 300 400 500 600 700 800 900 1000
FREQUENCY (MHz)
Figure 10. Output Third-Order Intercept (OIP3) at Output Level at 2 V p-p
Composite, RL = 200 Ω, VPOS = 3.3 V and VPOS = 5 V
Figure 13. IMD3 vs. Frequency, Over Temperature, Output Level at
2 V p-p Composite, RL = 200 Ω, VPOS = 3.3 V and VPOS = 5 V
60
50
40
30
–20
–30
–40
–50
–60
–70
5V
SUPPLY
3.3V
SUPPLY
–80
20
10
0
OIP3, 3.3V, +25°C, 2V p-p
OIP3, 5V, +25°C, 2V p-p
OIP3, 3.3V, +85°C, 2V p-p
OIP3, 5V, +85°C, 2V p-p
OIP3, 3.3V, –40°C, 2V p-p
OIP3, 5V, –40°C, 2V p-p
OIP3, 3.3V, +105°C, 2V p-p
OIP3, 5V, +105°C, 2V p-p
OIP3, 3.3V, +25°C, 1V p-p
OIP3, 5V, +25°C, 1V p-p
OIP3, 3.3V, +85°C, 1V p-p
OIP3, 5V, +85°C, 1V p-p
OIP3, 3.3V, –40°C, 1V p-p
OIP3, 5V, –40°C, 1V p-p
OIP3, 3.3V, +105°C, 1V p-p
OIP3, 5V, +105°C, 1V p-p
–90
–100
–110
–120
0
100 200 300 400 500 600 700 800 900 1000
FREQUENCY (MHz)
0
0.5
1.0
1.5
2.0
VCOM (V)
2.5
3.0
3.5
4.0
Figure 11. OIP3 vs. Frequency, Overtemperature, Output Level at 2 V p-p
Composite, RL = 200 Ω, VPOS = 3.3 V and VPOS = 5 V
Figure 14. IMD3 vs. VCOM, Output Level at 2 V p-p Composite, RL = 200 Ω,
POS = 3.3 V and VPOS = 5 V, Frequency = 100 MHz
V
Rev. C | Page 9 of 24
ADL5566
Data Sheet
–50
0
–20
–40
IMD3 100Ω LOAD
IMD3 150Ω LOAD
IMD3 200Ω LOAD
HD3, 5V, 25°C, 1V p-p
HD3, 3.3V, 25°C, 2V p-p
HD3, 5V, 25°C, 2V p-p
HD3, 3.3V, 25°C, 1V p-p
–55
–60
–60
–65
–70
–80
–40
–75
–80
–85
–100
–120
–140
–60
–90
–95
–80
–100
–105
–110
–115
–120
–100
–120
HD2, 3.3V, 25°C, 2V p-p
HD2, 5V, 25°C, 2V p-p
HD2, 3.3V, 25°C, 1V p-p
HD2, 5V, 25°C, 1V p-p
–160
0
50
100 150 200 250 300 350 400 450 500
FREQUENCY (MHz)
0
100 200 300 400 500 600 700 800 900 1000
FREQUENCY (MHz)
Figure 18. Harmonic Distortion (HD2/HD3) vs. Frequency,
Output Level at 2 V p-p Composite, RL = 200 Ω, VPOS = 3.3 V and VPOS = 5 V
Figure 15. IMD3 vs. Frequency, RL = 100 Ω, RL = 150 Ω, and RL = 200 Ω, VPOS = 3.3 V,
Input Common-Mode = 1.65 V, Output Common-Mode = 1.25 V, VOUT = 1.5 V p-p
0
–40
60
55
50
45
40
35
30
25
20
HD2, 3.3V, +25°C
HD2, 3.3V, +85°C
HD2, 3.3V, –40°C
HD2, 3.3V, +105°C
HD2, 5V, +25°C
HD2, 5V, +85°C
HD2, 5V, –40°C
HD2, 5V, +105°C
–20
–60
–80
–40
–100
–120
–140
–160
–60
–80
–100
–120
HD3, 3.3V, +25°C
HD3, 5V, +25°C
HD3, 5V, +85°C
HD3, 5V, –40°C
HD3, 5V, +105°C
HD3, 3.3V, +85°C
HD3, 3.3V, –40°C
HD3, 3.3V, +105°C
0
50
100 150 200 250 300 350 400 450 500
FREQUENCY (MHz)
0
50
100 150 200 250 300 350 400 450 500
FREQUENCY (MHz)
Figure 19. Harmonic Distortion (HD2/HD3) vs. Frequency,
Output Level at 2 V p-p Composite, RL = 200 Ω, VPOS = 3.3 V and VPOS = 5 V
Figure 16. Single-Ended OIP3 vs. Frequency, VPOS = 3.3 V,
2 V p-p Composite Output, RL = 200 Ω
–60
0
120
100
80
60
40
20
0
0
3.3V, HD2, 25°C
5V, HD2, 25°C
3.3V OIP2
5V OIP2
3.3V IMD2
5V IMD2
–20
–40
–60
–80
–100
–120
–80
–20
–40
–60
–80
–100
–120
–100
–120
–140
–160
–180
3.3V, HD3, 25°C
5V, HD3, 25°C
–2
0
2
4
6
8
10
0
100 200 300 400 500 600 700 800 900 1000
P
/TONE (dBm)
OUT
FREQUENCY (MHz)
Figure 17. OIP2/IMD2 vs. Frequency
Figure 20. Harmonic Distortion (HD2/HD3) vs. Output Power (POUT) per Tone,
Frequency = 200 MHz, RL = 200 Ω, VPOS = 3.3 V and VPOS = 5 V
Rev. C | Page 10 of 24
Data Sheet
ADL5566
–60
–65
0
HD2 AT 3.3V
HD3 AT 3.3V
HD2 AT 5.0V
HD3 AT 5.0V
HD2, 3.3V
HD3, 3.3V
HD2, 5V
HD3, 5V
–10
–20
–30
–40
–50
–60
–70
–80
–90
–100
–110
–70
–75
–80
–85
–90
–95
–100
–105
–110
0
100
200
300
400
500
0.5
1.0
1.5
2.0
2.5
3.0
FREQUENCY (MHz)
VCOM (V)
Figure 21. Harmonic Distortion (HD2/HD3) vs. VCOM, Output Level at
2 V p-p, RL = 200 Ω, VPOS = 3.3 V and VPOS = 5 V, Frequency = 100 MHz
Figure 24. Single-Ended Harmonic Distortion (HD2/HD3) vs. Frequency,
VPOS = 3.3 V and VPOS = 5 V, VOUT = 2 V p-p, RL = 200 Ω
–50
–80
–85
–90
HD2 100Ω LOAD
HD2 200Ω LOAD
–55
–60
–65
–70
–75
HD2
–95
–100
–105
–110
–115
–120
–80
IMD3
–85
–90
–95
HD3
–100
–105
–110
–115
–120
0
50
100 150 200 250 300 350 400 450 500
FREQUENCY (MHz)
0
1
2
3
4
5
6
FREQUENCY (MHz)
Figure 22. HD2 vs. Frequency, RL = 100 Ω and RL = 200 Ω, VPOS = 3.3 V, Input
Common-Mode = 1.65 V, Output Common-Mode = 1.25 V, VOUT = 1.5 V p-p
Figure 25. Low Frequency Distortion (HD2/HD3/IMD3) vs. Frequency,
Output Level at 2 V p-p, RL = 200 Ω, VPOS = 3.3 V
–50
HD3 200Ω LOAD
HD3 100Ω LOAD
–55
–60
–65
–70
–75
–80
–85
3
–90
–95
–100
–105
–110
–115
–120
2
2ns/DIV
0
50
100 150 200 250 300 350 400 450 500
FREQUENCY (MHz)
CH2 100mV/DIV 50Ω
CH3 500mV/DIV 50Ω
8G
8G
A CH3
1.1V
Figure 23. HD3 vs. Frequency, RL = 100 Ω and RL = 200 Ω, VPOS = 3.3 V, Input
Common-Mode = 1.65 V, Output Common-Mode = 1.25 V, VOUT = 1.5 V p-p
Figure 26. ENBLx Time Domain Response, VPOS = 3.3 V
Rev. C | Page 11 of 24
ADL5566
Data Sheet
0
–10
–20
–30
–40
–50
–60
–70
–80
–90
–100
1
CH1 400mV 2ns
A CH1
0V
10
100
1000
FREQUENCY (MHz)
Figure 30. Reverse Isolation (S12) vs. Frequency
Figure 27. Large Signal Pulse Response Using a Slow Transient Signal
Generator, 4 V p-p, VPOS = 3.3 V
60
55
50
45
40
35
30
25
20
15
10
5
220
2.0
1.8
1.6
1.4
1.2
1.0
0.8
0.6
0.4
0.2
0
RESITANCE
CAPACITANCE
210
200
190
180
170
160
150
140
130
120
0
10
10
100
1000
100
1000
FREQUENCY (MHz)
FREQUENCY (MHz)
Figure 31. S11 Equivalent RLC Parallel Network
Figure 28. Common-Mode Rejection Ratio (CMRR) vs. Frequency
20
18
16
14
12
10
8
10
9
8
7
6
5
4
3
2
1
0
1000
900
800
700
600
500
400
300
200
100
0
RESISTANCE
CAPACITANCE
6
4
2
0
10
100
1000
0
100 200 300 400 500 600 700 800 900 1000
FREQUENCY (MHz)
FREQUENCY (MHz)
Figure 32. S22 Equivalent RLC Parallel Network
Figure 29. Group Delay vs. Frequency
Rev. C | Page 12 of 24
Data Sheet
ADL5566
0
–5
85
80
75
70
65
60
–10
–15
–20
–25
–30
–35
–40
–45
–50
–55
–60
–65
–70
–75
–80
–85
–90
–95
5V
3.3V
–100
10M
100M
FREQUENCY (Hz)
1G
10G
–40
–20
0
20
40
60
80
100
TEMPERATURE (°C)
Figure 33. Output Referred Crosstalk, Channel A to Channel B, VPOS = 3.3 V,
VCOM = 1.65 V
Figure 34. ISUPPLY vs. Temperature, RL = 200 Ω, VPOS = 3.3 V and VPOS = 5 V
Rev. C | Page 13 of 24
ADL5566
Data Sheet
CIRCUIT DESCRIPTION
The ADL5566 is a high gain, fully differential dual amplifier/ADC
driver that uses a 2.8 V to 5 V supply. It provides a 16 dB gain
that can be reduced by adding external series resistors. The 3 dB
bandwidth is 4.5 GHz, and it has a differential input impedance of
160 Ω. It has a differential output impedance of 10 ꢀ and an
output common-mode adjust voltage of 1.1 V to 1.8 V.
product that results in distortion levels that are the best in the
industry for power consumed at frequencies beyond 100 MHz.
This amplifier achieves greater than −69 dBc IMD3 at 500 MHz
and −100 dBc at 200 MHz for 2 V p-p operation. In addition,
the ADL5566 can also deliver 5 V p-p operation under heavy
loads. The internal gain is set at 16 dB, and the part has a noise
figure of 6.5 dB and a RTI of 1.5 nV/√Hz. When comparing noise
figure and distortion performance, this amplifier delivers the
best in category spurious-free dynamic range (SFDR).
500Ω
80Ω
80Ω
5Ω
5Ω
0.1µF
The ADL5566 is very flexible in terms of I/O coupling. It can be
ac- or dc-coupled. For dc coupling, the output common-mode
voltage (VCOMx) can be adjusted (using the VCOMx pin) from
1.1 V to 1.8 V output for VCCx at 3.3 V and up to 3 V with VCCx
at 5 V. For the best distortion, the common-mode output should
not go below 1.25 V at VCCx equal to 3.3 V and 1.35 V for 5 V
VCCx operation. Note that the input common-mode voltage
slaves to the VCOMx output voltage when ac-coupled at the
inputs. For dc-coupled inputs, the input common-mode voltage
should also stay between 1.25 V and 1.8 V for a 3.3 V supply and
1.35 V to 3.5 V for a 5 V supply. Note again that, for ac-coupled
applications with series capacitors at the inputs, as in Figure 37,
the output common-mode voltage, VCOMx, sets the common-
mode input to the same level. Because of the wide input common-
mode range, this part can easily be dc-coupled to many types of
mixers, demodulators, and amplifiers. Forcing a higher input
VCOMx does not affect the output VCOMx in dc-coupled mode.
Note that, if the outputs are ac-coupled (see the ADC Interfacing
section), no external VCOMx adjust is required because the
amplifier common-mode outputs are set at VCCx/2.
+
0.1µF
RL
½ R
AC
S
½
ADL5566
–
½ R
S
0.1µF
0.1µF
500Ω
Figure 35. Basic Structure
The ADL5566 is composed of a dual fully differential amplifier
with on-chip feedback and feed-forward resistors. The gain is fixed
at 16 dB but can be reduced by adding two resistors in series with
the two inputs (see the Gain Adjustment and Interfacing section).
The amplifier is designed to provide a high differential open-loop
gain and has an output common-mode circuit that enables the
user to change the output common-mode voltage by applying a
voltage to a VCOMx pin. The amplifier is designed to provide
superior low distortion at frequencies to and beyond 300 MHz
with low noise and low power consumption. The low distortion
and noise are realized with a 3.3 V power supply at 140 mA.
The dual amplifier has an extremely high gain bandwidth (GBW)
Rev. C | Page 14 of 24
Data Sheet
ADL5566
APPLICATIONS INFORMATION
6 (VIN2), and the output pins, Pin 13 (VON2) and Pin 14
(VOP2), are biased by applying a voltage to VCOM2. If
BASIC CONNECTIONS
Figure 36 shows the basic connections for operating the ADL5566.
Apply a voltage between 3 V and 5 V to the VCC1 and VCC2
pins through a 5.1 nH inductor and decouple the supply side of the
inductor with at least one low inductance, 0.1 μF surface-mount
ceramic capacitor. In addition, decouple the VCOM1 and VCOM2
pins (Pin 21 and Pin 10) using a 0.1 μF capacitor. The ENBL1
and ENBL2 pins (Pin 22 and Pin 9) are tied to their amplifiers
VCC_x pin to enable each amplifier. A differential signal is
applied to Amplifier 1 through Pin 1 (VIN1) and Pin 2 (VIP1)
and to Amplifier 2 through Pin 5 (VIP2) and Pin 6 (VIN2).
Each amplifier has a gain of 16 dB.
VCOM2 is left open, VCOM2 equals ½ of VCC2. The ADL5566
can be ac-coupled as shown in Figure 36 or can be dc-coupled if
within the specified input and output common-mode voltage
ranges (see the Circuit Description section). To enable the
ADL5566, the ENBL1 and ENBL2 pins must be pulled high.
Pulling the ENBL1/ENBL2 pins low puts the ADL5566 in sleep
mode, reducing the current consumption to 7 mA at ambient.
A series 5.1 nH inductor can be connected to the VCCx pins with
the VCC decoupling capacitor connected to the VCC bus side (see
Figure 36 and Figure 53). This inductor with the internal
capacitance of the amplifier results in a two pole low-pass
network and reduces the amplifier VCC noise.
The input pins, Pin 1 (VIN1) and Pin 2 (VIP1), and the output
pins, Pin 18 (VON1) and Pin 17 (VOP1), are biased by
applying a voltage to Pin 21 (VCOM1). If VCOM1 is left open,
VCOM1 equals ½ of VCC1. The input pins, Pin 5 (VIP2) and Pin
VCC
+
10µF
0.01µF
5.1nH
VCC1
0.01µF
5.1nH
VCC2
11
20
EXPOSED PAD
R
F
0.01µF
VON1
18
21
½ R
0.01µF
0.01µF
S
R
G
VCOM1
0.01µF
VIP1
VIN1
2
1
BALANCED
LOAD
BALANCED
SOURCE
R
G
½ R
S
VOP1
17
R
0.01µF
F
ENBL1
ENBL2
22
9
VCC
VCC
ADL5566
R
F
0.01µF
VON2
13
10
½ R
0.01µF
S
R
G
VCOM2
VIP2
VIN2
5
6
BALANCED
LOAD
BALANCED
SOURCE
0.01µF
R
G
0.01µF
½ R
S
VOP2
14
R
0.01µF
F
NC
NC
3
24
4
7
8
12 15 16 19 23
NOTES
1. EXPOSED PADDLE IS INTERNALLY CONNECTED TO GND AND MUST BE SOLDERED
TO A LOW IMPEDANCE GROUND PLANE.
Figure 36. Basic Connections
Rev. C | Page 15 of 24
ADL5566
Data Sheet
VCC
+
INPUT AND OUTPUT INTERFACING
The ADL5566 can be configured as a differential input to
differential output driver, as shown in Figure 37. The 36 Ω
resistors, R1 and R2, combined with the ETC1-1-13 balun
transformer, provide a 50 ꢀ input match for the 160 Ω input
impedance. The input and output 0.1 μF capacitors isolate the
VCC/2 bias from the source and balanced load. The load should
equal 200 Ω to provide the expected ac performance (see the
Specifications section).
R2
0.1µF
0.1µF
0.1µF
R
½ RL
½ RL
S
½
77Ω
ADL5566
AC
–
+
0.1µF
R1
30Ω
Figure 39. Single-Ended Input to Differential Output Configuration
VCC
The single-ended gain configuration of the ADL5566 is dependent
on the source impedance and load, as shown in Figure 40.
ETC1-1-13
+
0.1µF
0.1µF
0.1µF
0.1µF
50Ω
AC
R2
½ RL
½ RL
½
ADL5566
500Ω
–
80Ω
80Ω
5Ω
5Ω
+
R1
R2
0.1µF
0.1µF
0.1µF
R
½ RL
½ RL
S
½
77Ω
ADL5566
AC
Figure 37. Differential Input to Differential Output Configuration
–
The differential gain of the ADL5566 is dependent on the source
impedance and load, as shown in Figure 38.
+
0.1µF
R1
500Ω
30Ω
500Ω
Figure 40. Single-Ended Input Loading Circuit
80Ω
80Ω
5Ω
5Ω
0.1µF
The single-ended gain can be determined by the following two
equations:
+
0.1µF
RL
½ R
AC
S
½
ADL5566
R2131
R2 131
RMATCH
–
½ R
S
0.1µF
RMATCH RS
RMATCH
RL
10 RL
500
R2
RS R2
0.1µF
500Ω
A
V1
RS R2
RS R2
80
Figure 38. Differential Input Loading Circuit
The differential gain can be determined by
500 RL
80 10 RL
GAIN ADJUSTMENT AND INTERFACING
The effective gain of the ADL5566 can be reduced by adding two
resistors in series with the inputs to reduce the 16 dB gain.
(1)
AV
Single-Ended Input to Differential Output
500Ω
The ADL5566 can also be configured in a single-ended input to
differential output driver, as shown in Figure 39. In this
R
SERIES
80Ω
80Ω
5Ω
5Ω
+
configuration, the gain of the part is reduced due to the application
of the signal to only one side of the amplifier. The input and output
0.1 μF capacitors isolate the VCC/2 bias from the source and the
balanced load. R2 is used to match the single-ended input
impedance of the amplifier (131 Ω) with the 50 Ω source. R1 is
selected to balance the input of the amplifier. See the Application
Note AN-0990 for more information on terminating single-ended
inputs. The performance for this configuration is shown in
Figure 16 and Figure 24.
0.1µF
RL
0.1µF
R
½ R
AC
S
½
ADL5566
SHUNT
0.1µF
–
½ R
S
R
SERIES
0.1µF
500Ω
Figure 41. Gain Adjustment Using a Series Resistor Show
Rev. C | Page 16 of 24
Data Sheet
ADL5566
To find RSERIES for a given AV gain and RL, use the following:
The necessary shunt component, RSHUNT, to match to the source
impedance, RS, can be expressed with the following:
1
(5)
RSHUNT
=
1
1
−
RS 2RSERIES +160
500
RSERIES
=
−80
(3)
The voltage gain for multiple shunt resistor values are summarized
in Table 5. The source resistance and input impedance need
careful attention when using Equation 5. The reactance of the
input impedance of the ADL5566 and the ac coupling capacitors
must be considered before assuming that they make a negligible
contribution.
AV
RL
10 + RL
To calculate the AV gain for a given RSERIES and RL, use the following:
–50
HD2 3.3V
500
SERIES +80
R
L
–55
–60
HD3 3.3V
IMD 3.3V
HD2 5V
HD3 5V
IMD 5V
(4)
AGAIN
=
×
R
10 + R
L
20
19
18
17
16
15
14
13
12
11
10
9
–65
–70
–75
–80
–85
–90
–95
8
–100
–105
–110
–115
–120
7
6
5
4
3
2
1
0
0
50
100 150 200 250 300 350 400 450 500
FREQUENCY (MHz)
–1
–2
–3
–4
–5
Figure 43. IMD, HD2, and HD3 vs. Frequency, AV = 6 dB, 2 V p-p Output,
POS = 3.3 and VPOS = 5 V
1M
10M
100M
1G
10G
V
FREQUENCY (Hz)
Figure 42. SDD21, VPOS = 3.3 V, Three Gains, 25°C
Table 5. Differential Gain Adjustment Using Series Resistor
Target Gain (dB)
Actual Gain (dB)
RS (Ω)
50
50
50
50
50
50
50
50
50
50
50
50
50
50
50
50
RSERIES (Ω)1
396.2
344.4
298.3
257.1
220.5
187.8
158.7
132.7
109.6
89
70.6
54.2
39.6
26.6
15
4.8
RSHUNT (Ω)1
52.8
53.1
53.5
54
54.5
55.1
55.8
56.7
57.6
58.7
60
0
−0.1
1
+1.2
2
+2.1
3
+2.9
4
+4.1
5
+5.1
6
+6.1
7
+6.9
8
+8.1
9
+8.9
10
11
12
13
14
15
+10
+11.1
+12
+12.8
+14
61.4
63.2
65.3
67.9
70.9
+15.1
+15.8
16
50
0
72.7
1 The resistor values are rounded to the nearest real resistor value.
Rev. C | Page 17 of 24
ADL5566
Data Sheet
FUNDAMENTAL1 = –7.03dBFS
FUNDAMENTAL2 = –7.05dBFS
IMD (2f1 – f2) = –90.53dBc
IMD (2f2 + f1) = –96.81dBc
NOISE FLOOR = –114.703dB
ADC INTERFACING
0
–15
The ADL5566 is a dual high output linearity amplifier that is
optimized for ADC interfacing. One option of applying the
ADL5566 to drive an ADC is shown in Figure 47. The wideband
1:1 transmission line balun provides a differential input to the
amplifier, and the 36 Ω resistors provide a 50 Ω match to the
source. The ADL5566 is ac-coupled from the input and output
to avoid common-mode loading. A reference voltage is
required to bias the AD9268 inputs and is delivered through
the 200 Ω resistors. These, in parallel with the 400 Ω resistor,
create the low frequency amplifier load of 200 Ω. The 56 nH
inductors and the 56 pF capacitor are used to create a 70 MHz
low-pass filter. The two 25 Ω resistors are added to raise the
ADL5566 output impedance, which reduces peaking when the
filter drives a light load. The two 25 Ω resistors provide isolation to
the switching currents of the ADC sample-and-hold circuitry.
The AD9268 dual ADC presents a 6 kΩ differential load
impedance and requires a 1 V p-p to 2 V p-p input signal to
reach full scale. The system frequency response is shown in
Figure 46. By applying a 2 V p-p, 32 MHz single-tone signal from
the ADL5566 in a gain of 16 dB, an SFDR of 94.6 dBc is achieved.
By applying two half scale signals of 32 MHz and 33 MHz from
the ADL5566 in a gain of 16 dB, an SFDR of 90.5 dBc is
realized.
–30
–45
–60
–75
–90
–105
–120
–135
–150
0
6
12
18
24
30
36
42
48
54
60
FREQUENCY (MHz)
Figure 45. Measured Two-Tone Performance of the Circuit in Figure 47 for a
32 MHz and 33 MHz Input Signals
2
1
0
–1
–2
–3
–4
–5
–6
–7
–8
–9
–10
–11
–12
–13
–14
–15
–16
–17
–18
–19
–20
0
SNR = 74.28dB
FUND FREQ = 32.123MHz
FUND POWER = –1.014dBFS
–15
SECOND HARM = –94.629dBc
THIRD HARM = –95.19dBc
FOURTH HARM = –99.98dBc
FIFTH HARM = –104.971dBc
SIXTH HARM = –107.105dBc
–30
–45
0
20
40
60
80
100
120
140
160
FREQUENCY (MHz)
–60
Figure 46. Measured Relative Frequency Response of the Wideband ADC
Interface Depicted in Figure 47
–75
–90
3
+
2
–105
–120
–135
–150
4
5
6
0
6
12
18
24
30
36
42
48
54
60
FREQUENCY (MHz)
Figure 44. Measured Single-Tone Performance of the Circuit in Figure 47 for a
32 MHz Input Signal
VCC
0.1µF
ETC1-1
VIN_1
VIP_1
25Ω
25Ω
25Ω
+
0.1µF
0.1µF
50Ω
AC
36Ω
36Ω
200Ω
½
16
AD9268
V
56pF
REF
400Ω
ADL5566
SIDE A
200Ω
25Ω
–
0.1µF
Figure 47. Wideband ADC Interfacing Example Featuring the AD9268
Rev. C | Page 18 of 24
Data Sheet
ADL5566
DC-COUPLED RECEIVER APPLICATION
The ADL5566 is well suited for dc-coupled applications, such
as zero-IF direct conversion receivers. An example receiver
configuration is shown in Figure 48, consisting of the ADL5380
quadrature demodulator and the ADL5566 dual differential
amplifier. This is an ideal combination because of the wide RF
input bandwidth from 400 MHz to 6 GHz, the high linearity of the
ADL5566, and when operating on a 5 V supply, level shifting to
align the common-mode voltage is not required.
performance. When using the ADL5566 as shown in Figure 48,
the OIP3s at the outputs are improved due to the high OIP3 of
the amplifier pair (see Table 6). In a real-world receiver where
blockers are present, it is advantageous to insert a low-pass
filter between the ADL5380 and the ADL5566 to remove
these undesired signals.
If the ADL5566 is followed by an ADC, insert an antialiasing
filter between the ADL5566 and the ADC to prevent broadband
noise from aliasing back in band. For more information on this
interface, see the ADC Interfacing section.
The interface between the ADL5380 and the ADL5566 is
straight forward because the impedance presented by the
ADL5566 is sufficiently high enough to permit directly
connecting the two devices without any degradation in
The cascade of the performance of the circuit shown in Figure 48 is
presented in Table 6.
V
S
VCC
+
0.1µF
0.1µF
0.1µF
10µF
0.01µF
5.1nH
0.01µF
5.1nH
VCC2
100pF
100pF
100pF
1.5kΩ
VCC1
11
20
6
13
24
19
R
F
NC
12
7
0.01µF
ILO
VON1
4
3
18
21
R
R
ENBL
G
VCOM1
0.01µF
IHI
VIP1
VIN1
2
1
BALANCED
LOAD
GND3
G
23
9
VOP1
17
100pF
100pF
R
0.01µF
F
TC1-1-13
RFIP
RFIN
ENBL1
ENBL2
22
21
100pF
100pF
22
9
TC1-1-13
VCC
VCC
LOIP
90°
ADL5566
0Ω
R
F
0°
LOIN
R4
0Ω
10
20
0.01µF
VON2
GND3
13
10
GND3
1
2
R
G
VCOM2
VIP2
VIN2
5
6
BALANCED
LOAD
0.01µF
QHI
GND1
GND1
16
15
R
G
VOP2
NC
QLO
14
24
R
0.01µF
F
5
NC
GND3
3
18
4
7
8
12 15 16 19 23
8
11
14
17
Figure 48. DC-Coupled Interface Example Featuring the ADL5380
Table 6. Cascade Performance of the ADL5380 and ADL5566
IF Frequency = 200 MHz, RL = 200 Ω, VOUT = 2 V p-p Composite
Frequency (MHz) HD2 (dBc) HD3 (dBc) OIP3 (dBm) ADL5380 OIP3 (dBm)1 OIP2 (dBm) Voltage Gain (dB) Power Gain (dB)
900
1900
2700
−79.3
−82.2
−80.7
−84.2
−80.5
−73.9
44.9
40.8
39.6
26.2
26.5
25.7
91.8
83.9
75.6
18.1
18.1
18.1
12.0
12.0
12.0
1 Output referred IP3 of the ADL5380, PIN = −14 dBm, and RL = 200 Ω.
Rev. C | Page 19 of 24
ADL5566
Data Sheet
LAYOUT CONSIDERATIONS
High-Q inductive drives and loads, as well as stray transmission
line capacitance in combination with package parasitics, can
potentially form a resonant circuit at high frequencies, resulting
in excessive gain peaking or possible oscillation. If RF transmission
lines connecting the input or output are used, design them such
that stray capacitance at the input/output pins is minimized. In
many board designs, the signal trace widths should be minimal
where the driver/receiver is no more than one-eighth of the wave-
length from the amplifier. This nontransmission line configuration
requires that underlying and adjacent ground and low impedance
planes be dropped from the signal lines.
VCC
+
0.1µF
5.1nH
VIN_1
0.1µF
ETC1-1
ETC1-1
84.5Ω
34.8Ω
+
0.1µF
0.1µF
50Ω
AC
36Ω
36Ω
½
50Ω
ANALYZER
ADL5566
AMPLIFIER 1
VIP_1
84.5Ω
34.8Ω
–
0.1µF
Figure 49. General-Purpose Characterization Circuit
VCC
+
0.1µF
5.1nH
0.1µF
+
0.1µF
+
VIN_1
VIP_1
50Ω
50Ω
PORT 1
PORT 3
+
50Ω
AC
50Ω
AC
½
ADL5566
AMPLIFIER 1
36Ω
PORT 2
–
PORT 4
+
+
0.1µF
0.1µF
50Ω
AC
50Ω
AC
Figure 50. Differential Characterization Circuit Using Agilent E8357A Four-Port PNA
INPUT
COMMON-MODE V
ADJUST
VCC
+
0.1µF
2kΩ 2kΩ
0.1µF
5.1nH
VIN_1
0.1µF
ETC1-1
84.5Ω
34.8Ω
ETC1-1
+
+
50Ω
AC
36Ω
36Ω
50Ω
ANALYZER
ADL5566
AMPLIFIER 1
84.5Ω
34.8Ω
VIP_1
–
0.1µF
0.1µF
VCOM
OUTPUT
Figure 51. Distortion Measurement Circuit for Various Common-Mode Voltages
Rev. C | Page 20 of 24
Data Sheet
ADL5566
SOLDERING INFORMATION AND RECOMMENDED
LAND PATTERN
EVALUATION BOARD
Figure 53 shows the schematic of the ADL5566 evaluation board.
The board is powered by a single supply in the 3 V to 5 V range.
The power supply is decoupled by 10 µF and 0.1 µF capacitors.
The L1 and L2 inductors decouple the ADL5566 from the power
supply.
Figure 52 shows the recommended land pattern for the ADL5566.
The ADL5566 is contained in a 4 mm × 4 mm LFCSP package,
which has an exposed ground paddle (EPAD). This paddle is
internally connected to the ground of the chip. To minimize
thermal impedance and ensure electrical performance, solder
the paddle to the low impedance ground plane on the printed
circuit board (PCB). To further reduce thermal impedance, it
is recommended that the ground planes on all layers under the
paddle be stitched together with vias.
Table 7 details the various configuration options of the evaluation
board. Figure 54 and Figure 55 show the component and circuit
side layouts of the evaluation board.
The balanced input and output interfaces are converted to single
ended with a pair of baluns (M/A-COM ETC1-1-13). The baluns
at the input, T1 and T2, provide a 50 Ω single-ended-to-differential
transformation. The output baluns, T3 and T4, and the matching
components are configured to provide a 200 Ω to 50 Ω impedance
transformation with an insertion loss of about 11 dB.
For more information on land pattern design and layout, refer
to the AN-772 Application Note, A Design and Manufacturing
Guide for the Lead Frame Chip Scale Package (LFCSP).
This land pattern, on the ADL5566 evaluation board, provides a
measured thermal resistance (θJA) of 34.0°C/W. To measure θJA,
the temperature at the top of the LFCSP package is found with
an IR temperature gun. Thermal simulation suggests a junction
temperature 1.5°C higher than the top of package temperature.
With additional ambient temperature and I/O power measure-
ments, θJA can be determined.
91 MILS
13 MILS
13.7 MILS
39 MILS
19.7 MILS
12 MILS
Figure 52. Recommended Land Pattern
Rev. C | Page 21 of 24
ADL5566
Data Sheet
ENBL_1
V
VCOM-1
C6
CC
V
CC
+
GND
0.1µF
V
C7
0.1µF
POS
V
CC
C21
10µF
C3
0.1µF
L2
5.1nH
2
2
C10
DNI
C12
DNI
24
23
22
21
20
19
VOP1
C18
R18
R10
36Ω
C13
VIN1
R14
R5
0Ω
0.01µF
34.8Ω
0.01µF
84.5Ω
T1
T3
VON1
VIIN1
VIP1
NC
18
17
16
15
1
C17
R27
DNI
R8
0Ω
VON1
DNI
0.01µF
R1
VIP1
VIP2
VOP1
NC
2
3
4
5
6
DNI
DNI
R13
84.5Ω
R25
R9
36Ω
R17
34.8Ω
C14
0.01µF
ADL5566
R3
0Ω
0Ω
VON2
NC
NC
C20
0.01µF
C15
0.01µF
R20
34.8Ω
R11
36Ω
R16
84.5Ω
R21
0Ω
EXPOSED PADDLE
T2
T4
VOP2 14
VIP2
VIN2
DNI
R28
R24
0Ω
R2
DNI
VOP2
DNI
VIN2
DNI
VON2
12
13
R19
34.8Ω
R15
84.5Ω
R26
0Ω
R12
36Ω
C19
0.01µF
R4
0Ω
C16
0.01µF
7
8
9
10
11
2
2
C1
DNI
C11
DNI
L1
5.1nH
C4
0.1µF
V
POS
C2
0.1µF
C5
0.1µF
ENBL_2
VCOM-2
V
CC
Figure 53. Evaluation Board Schematic
Table 7. Evaluation Board Configuration Options
Component
Description
Default Condition
VPOS, GND
Ground and supply test loops.
VPOS, GND = installed
C5, C7, C21, L1, Power supply decoupling. The supply decoupling consists of a 10 μF capacitor (C21) and C21 = 10 μF (Size D),
L2
two 0.1ꢀF capacitors, C5 and C7, connected between the supply lines and ground.
L1 and L2 decouple the ADL5566 from the power supply.
C5, C7 = 0.1 μF (Size 0402),
L1, L2 = 5.1 nH (Size 0603)
VIN1, VIP1, VIP2, Input interface. The SMA labeled VIN1 is the input to Amplifier 1. T1 is a 1:1
VIN2, R1, R2, R3, impedance ratio balun to transform a single-ended input into a balanced differential
VIN1, VIP2 = installed,
VIP1, VIN2 = not installed,
R1, R2 = DNI,
R4, R5, R8, R9,
R10, R11, R12,
R21, R24, C13,
C1, C12, C14,
C15, C16, T1, T2
signal. Removing R3, installing R1 (0 Ω), and installing an SMA connector (VIP1) allow
driving from a differential source. C13 and C14 provide ac coupling. C12 is an
optional bypass capacitor. R9 and R10 provide a differential 50 Ω input termination. The (Size 0402),
SMA labeled VIP2 is the input to Amplifier 2. T2 is a 1:1 impedance ratio balun to
transform a single-ended input into a balanced differential signal. Removing R4,
installing R2 (0 Ω), and installing an SMA connector (VIN2) allow driving from a
R3, R4, R5, R8, R21, R24 = 0 Ω
R9, R10, R11, R12 = 36 Ω (Size 0402),
C13, C14, C15, C16 = 0.01 μF
(Size 0402),
differential source. C15 and C16 provide ac coupling. C1 is an optional by pass capacitor. C1, C12 = DNI,
R11 and R12 provide a differential 50 Ω input termination.
T1, T2 = ETC1-1-13 (M/A-COM)
VOP1, VON1,
VON2, VOP2,
C10, C11, C17,
C18, C19, C20,
R13, R14, R15,
R16, R17, R18,
R19, R20, R25,
R26, R27, R28,
T3, T4
Output interface. The SMA labeled VOP1 is the output for Amplifier 1. T3 is a 1:1
impedance ratio balun used to transform a balanced differential signal to a single-
ended signal. Removing R25, installing R27 (0 Ω), and installing an SMA connector
(VON1) allow differential loading. C10 is an optional bypass capacitor. C17 and C18
provide ac coupling. R13, R14, R17, and R16 are provided for generic placement of
matching components.
VOP1, VON2 = installed,
VON1, VOP2 = not installed,
R13, R14, R15, R16 = 84.5 Ω
(Size 0402),
R17, R18, R19, R20 = 34.8 Ω
(Size 0402),
The SMA labeled VON2 is the output for Amplifier 2. T4 is a 1:1 impedance ratio balun
R25, R26 = 0 Ω (Size 0402),
used to transform a balanced differential signal to a single-ended signal. Removing R26, R27, R28 = DNI (Size 0402),
installing R28 (0 Ω), and installing an SMA connector (VOP2) allow differential loading. C10, C11 = DNI (Size 0402),
C11 is an optional bypass capacitor. C19 and C20 provide ac coupling. R15, R16, R19, C17, C18 = 0.01 μF (Size 0402),
and R20 are provided for generic placement of matching components.
The evaluation board is configured to provide a 200 Ω to 50 Ω impedance
transformation with an insertion loss of 11 dB.
C19, C20 = 0.01 ꢀF (Size 0402),
T3, T4 = ETC1-1-13 (M/A-COM)
Rev. C | Page 22 of 24
Data Sheet
ADL5566
Component
Description
Default Condition
ENBL_1, ENBL_2 = installed,
ENBL_1,
Device enable. ENBL_1 is the enable for Amplifier 1. Connecting a jumper between
ENBL_2, C3, C4 Pin 2 and VPOS enables Amplifier 1. C3 is a bypass capacitor. ENBL_2 is the enable for C3, C4 = 0.1 µF (Size 0402)
Amplifier 2. Connecting a jumper between Pin 2 and VPOS enables Amplifier 2. C4 is
a bypass capacitor.
VCOM-1,
Common-mode voltage interface. VCOM1 is the common-mode interface for
VCOM-1, VCOM-2 = installed
C2, C6 = 0.1 µF (Size 0402)
VCOM-2, C2, C6 Amplifier 1. A voltage applied to this pin sets the common-mode voltage of the output
of Amplifier 1. VCOM2 is the common-mode interface for Amplifier 2. A voltage applied
to this pin sets the common-mode voltage of the output of Amplifier 2. Typically
decoupled to ground with a 0.1 µF capacitor (C2 and C6). With no reference applied,
input and output common mode float to midsupply (VCC/2).
Figure 55. Layout of Evaluation Board, Circuit Side
Figure 54. Layout of Evaluation Board, Component Side
Rev. C | Page 23 of 24
ADL5566
Data Sheet
OUTLINE DIMENSIONS
DETAIL A
(JEDEC 95)
4.10
4.00 SQ
3.90
0.30
0.25
0.20
PIN 1
INDICATOR
AREA
PIN 1
IONS
INDICATOR AR EA OP T
(SEE DETAIL A)
24
19
18
1
0.50
BSC
2.44
2.30 SQ
2.16
EXPOSED
PAD
13
12
6
7
0.50
0.40
0.30
0.20 MIN
TOP VIEW
SIDE VIEW
BOTTOM VIEW
0.80
0.75
0.70
FOR PROPER CONNECTION OF
THE EXPOSED PAD, REFER TO
THE PIN CONFIGURATION AND
FUNCTION DESCRIPTIONS
0.05 MAX
0.02 NOM
COPLANARITY
0.08
SECTION OF THIS DATA SHEET.
SEATING
PLANE
0.203 REF
COMPLIANT TO JEDEC STANDARDS MO-220-WGGD-8
Figure 56. 24-Lead Lead Frame Chip Scale Package [LFCSP]
4 mm × 4 mm Body and 0.75 mm Package Height
(CP-24-14)
Dimensions shown in millimeters
ORDERING GUIDE
Model1
Temperature Range
Package Description
Package Option
ADL5566ACPZ-R7
ADL5566-EVALZ
−40°C to +85°C
24-Lead Lead Frame Chip Scale Package [LFCSP], 7” Tape and Reel
Evaluation Board
CP-24-14
1 Z = RoHS Compliant Part.
©2012–2019 Analog Devices, Inc. All rights reserved. Trademarks and
registered trademarks are the property of their respective owners.
D10916-0-8/19(C)
Rev. C | Page 24 of 24
相关型号:
ADL5570ACPZ-R7
2300MHz - 2400MHz RF/MICROWAVE WIDE BAND LOW POWER AMPLIFIER, 4 X 4 MM, ROHS COMPLIANT, LFCSP, 16 PIN
ROCHESTER
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