ADP1612-5-EVALZ [ADI]
650 kHz /1.3 MHz Step-Up PWM DC-to-DC Switching Converters; 650千赫/1.3 MHz升压PWM直流 - 直流开关转换器
| 型号： | ADP1612-5-EVALZ |
| 厂家： | 
ADI |
| 描述： | 650 kHz /1.3 MHz Step-Up PWM DC-to-DC Switching Converters |
| 文件： | 总28页 (文件大小：1262K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
650 kHz /1.3 MHz Step-Up
PWM DC-to-DC Switching Converters
ADP1612/ADP1613
FEATURES
TYPICAL APPLICATION CIRCUIT
L1
Current limit
1.4 A for the ADP1612
2.0 A for the ADP 1613
Minimum input voltage
1.8 V for the ADP1612
2.5 V for the ADP1613
Pin-selectable 650 kHz or 1.3 MHz PWM frequency
Adjustable output voltage up to 20 V
Adjustable soft start
ADP1612/
D1
ADP1613
V
V
OUT
IN
6
3
7
8
5
2
1
VIN
EN
SW
FB
ON
R1
R2
OFF
C
IN
1.3MHz
650kHz
(DEFAULT)
FREQ
SS
COMP
C
OUT
GND
4
R
COMP
C
SS
Undervoltage lockout
Thermal shutdown
C
COMP
8-lead MSOP
Figure 1. Step-Up Regulator Configuration
APPLICATIONS
TFT LCD bias supplies
Portable applications
Industrial/instrumentation equipment
100
GENERAL DESCRIPTION
V
= 5V
IN
fSW = 1.3MHz
= 25°C
The ADP1612/ADP1613 are step-up dc-to-dc switching con-
verters with an integrated power switch capable of providing
an output voltage as high as 20 V. With a package height of less
than 1.1 mm, the ADP1612/ADP1613 are optimal for space-
constrained applications such as portable devices or thin film
transistor (TFT) liquid crystal displays (LCDs).
90
80
70
T
A
60
50
40
The ADP1612/ADP1613 operate in current mode pulse-width
modulation (PWM) with up to 94% efficiency. Adjustable
soft start prevents inrush currents when the part is enabled.
The pin-selectable switching frequency and PWM current-mode
architecture allow for excellent transient response, easy noise
filtering, and the use of small, cost-saving external inductors
and capacitors. Other key features include undervoltage lockout
(UVLO), thermal shutdown (TSD), and logic controlled enable.
ADP1612, V
ADP1612, V
ADP1613, V
ADP1613, V
= 12V
OUT
OUT
OUT
OUT
= 15V
= 12V
= 15V
30
1
10
100
1k
LOAD CURRENT (mA)
Figure 2. ADP1612/ADP1613 Efficiency for Various Output Voltages
The ADP1612/ADP1613 are available in the lead-free
8-lead MSOP.
Rev. A
Information furnished by Analog Devices is believed to be accurate and reliable. However, no
responsibility is assumed by Analog Devices for its use, nor for any infringements of patents or other
rights of third parties that may result from its use. Specifications subject to change without notice. No
license is granted by implication or otherwise under any patent or patent rights of Analog Devices.
Trademarks and registeredtrademarks arethe property of their respective owners.
One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A.
Tel: 781.329.4700
Fax: 781.461.3113
www.analog.com
©2009 Analog Devices, Inc. All rights reserved.
ADP1612/ADP1613
TABLE OF CONTENTS
Features .............................................................................................. 1
UnderVoltage Lockout (UVLO)............................................... 12
Enable/Shutdown Control ........................................................ 12
Applications Information.............................................................. 13
Setting the Output Voltage........................................................ 13
Inductor Selection...................................................................... 13
Choosing the Input and Output Capacitors ........................... 13
Diode Selection........................................................................... 14
Loop Compensation .................................................................. 14
Soft Start Capacitor.................................................................... 15
Typical Application Circuits ......................................................... 16
Step-Up Regulator...................................................................... 16
Step-Up Regulator Circuit Examples....................................... 16
SEPIC Converter ........................................................................ 22
TFT LCD Bias Supply................................................................ 22
PCB Layout Guidelines.................................................................. 24
Outline Dimensions....................................................................... 25
Ordering Guide .......................................................................... 25
Applications....................................................................................... 1
Typical Application Circuit ............................................................. 1
General Description......................................................................... 1
Revision History ............................................................................... 2
Specifications..................................................................................... 3
Absolute Maximum Ratings............................................................ 4
Thermal Resistance ...................................................................... 4
Boundary Condition.................................................................... 4
ESD Caution.................................................................................. 4
Pin Configuration and Function Descriptions............................. 5
Typical Performance Characteristics ............................................. 6
Theory of Operation ...................................................................... 11
Current-Mode PWM Operation.............................................. 11
Frequency Selection ................................................................... 11
Soft Start ...................................................................................... 11
Thermal Shutdown (TSD)......................................................... 12
REVISION HISTORY
9/09—Rev. 0 to Rev. A
Changes to Figure 45...................................................................... 17
Changes to Figure 48 and Figure 51............................................. 18
Changes to Figure 54 and Figure 57............................................. 19
Changes to Figure 60 and Figure 63............................................. 20
Changes to Figure 66 and Figure 69............................................. 21
Changes to Figure 72...................................................................... 22
Changes to Ordering Guide .......................................................... 25
4/09—Revision 0: Initial Version
Rev. A | Page 2 of 28
ADP1612/ADP1613
SPECIFICATIONS
VIN = 3.6 V, unless otherwise noted. Minimum and maximum values are guaranteed for TJ = −40°C to +125°C. Typical values specified
are at TJ = 25°C. All limits at temperature extremes are guaranteed by correlation and characterization using standard statistical quality
control (SQC), unless otherwise noted.
Table 1.
Parameter
Symbol Conditions
Min
Typ
Max
Unit
SUPPLY
Input Voltage
VIN
ADP1612
ADP1613
1.8
2.5
5.5
5.5
V
V
Quiescent Current
Nonswitching State
IQ
VFB = 1.5 V, FREQ = VIN
VFB = 1.5 V, FREQ = GND
VEN = 0 V
FREQ = VIN, no load
FREQ = GND, no load
VEN = 3.6 V
900
700
0.01
4
2.2
3.3
1350
1300
2
5.8
4
μA
μA
μA
mA
mA
μA
Shutdown
Switching State1
IQSHDN
IQSW
Enable Pin Bias Current
OUTPUT
IEN
7
Output Voltage
Load Regulation
REFERENCE
VOUT
VIN
20
V
ILOAD = 10 mA to 150 mA, VIN = 3.3 V, VOUT = 12 V
0.1
mV/mA
Feedback Voltage
Line Regulation
ERROR AMPLIFIER
Transconductance
Voltage Gain
VFB
1.2041 1.235 1.2659
V
%/V
ADP1612, VIN = 1.8 V to 5.5 V; ADP1613, VIN = 2.5 V to 5.5 V
0.07
0.24
50
GMEA
AV
ΔI = 4 μA
80
60
1
μA/V
dB
nA
FB Pin Bias Current
SWITCH
VFB = 1.3 V
SW On Resistance
SW Leakage Current
Peak Current Limit2
RDSON
ICL
ISW = 1.0 A
VSW = 20 V
ADP1612, duty cycle = 70%
ADP1613, duty cycle = 70%
130
0.01
1.4
300
10
1.9
2.5
mΩ
μA
A
0.9
1.3
2.0
A
OSCILLATOR
Oscillator Frequency
fSW
FREQ = GND
FREQ = VIN
COMP = open, VFB = 1 V, FREQ = VIN
FREQ = 3.6 V
500
1.1
88
650
1.3
90
5
720
1.4
kHz
MHz
%
Maximum Duty Cycle
FREQ Pin Current
DMAX
IFREQ
8
ꢀA
EN/FREQ LOGIC THRESHOLD
Input Voltage Low
Input Voltage High
ADP1612, VIN = 1.8 V to 5.5 V; ADP1613, VIN = 2.5 V to 5.5 V
VIL
VIH
0.3
V
V
1.6
3.4
SOFT START
SS Charging Current
SS Voltage
ISS
VSS
VSS = 0 V
VFB = 1.3 V
5
1.2
6.2
μA
V
UNDERVOLTAGE LOCKOUT (UVLO)
Undervoltage LockoutThreshold
ADP1612, VIN rising
ADP1612, VIN falling
ADP1613, VIN rising
ADP1613, VIN falling
1.70
1.62
2.25
2.16
V
V
V
V
THERMAL SHUTDOWN
Thermal Shutdown Threshold
Thermal Shutdown Hysteresis
150
20
°C
°C
1 This parameter specifies the average current while switching internally and with SW (Pin 5) floating.
2 Current limit is a function of duty cycle. See the Typical Performance Characteristics section for typical values over operating ranges.
Rev. A | Page 3 of 28
ADP1612/ADP1613
ABSOLUTE MAXIMUM RATINGS
Table 2.
THERMAL RESISTANCE
Junction-to-ambient thermal resistance (θJA) of the package is
specified for the worst-case conditions, that is, a device soldered
in a circuit board for surface-mount packages. The junction-to-
ambient thermal resistance is highly dependent on the application
and board layout. In applications where high maximum power
dissipation exists, attention to thermal board design is required.
The value of θJA may vary, depending on PCB material, layout,
and environmental conditions.
Parameter
Rating
VIN, EN, FB to GND
FREQ to GND
COMP to GND
SS to GND
−0.3 V to +6 V
−0.3 V to VIN + 0.3 V
1.0 V to 1.6 V
−0.3 V to +1.3 V
21 V
SW to GND
Operating Junction Temperature Range −40°C to +125°C
Storage Temperature Range
Soldering Conditions
ESD (Electrostatic Discharge)
Human Body Model
−65°C to +150°C
JEDEC J-STD-020
Table 3.
Package Type
8-Lead MSOP
2-Layer Board1
4-Layer Board1
θJA
θJC
Unit
5 kV
206.9
162.2
44.22
44.22
°C/W
°C/W
Stresses above those listed under Absolute Maximum Ratings
may cause permanent damage to the device. This is a stress
rating only; functional operation of the device at these or any
other conditions above those indicated in the operational
section of this specification is not implied. Exposure to absolute
maximum rating conditions for extended periods may affect
device reliability.
1 Thermal numbers per JEDEC standard JESD 51-7.
BOUNDARY CONDITION
Modeled under natural convection cooling at 25°C ambient
temperature, JESD 51-7, and 1 W power input with 2- and
4-layer boards.
Absolute maximum ratings apply individually only, not in
combination.
ESD CAUTION
Rev. A | Page 4 of 28
ADP1612/ADP1613
PIN CONFIGURATION AND FUNCTION DESCRIPTIONS
COMP
FB
1
2
3
4
8
7
6
5
SS
ADP1612/
ADP1613
TOP VIEW
FREQ
VIN
EN
(Not to Scale)
GND
SW
Figure 3. Pin Configuration
Table 4. Pin Function Descriptions
Pin No.
Mnemonic
COMP
FB
Description
1
2
Compensation Input. Connect a series resistor-capacitor network from COMP to GND to compensate the regulator.
Output Voltage Feedback Input. Connect a resistive voltage divider from the output voltage to FB to set the
regulator output voltage.
3
4
5
EN
GND
SW
Enable Input. Drive EN low to shut down the regulator; drive EN high to turn on the regulator.
Ground.
Switching Output. Connect the power inductor from the input voltage to SW and connect the external rectifier
from SW to the output voltage to complete the step-up converter.
6
7
8
VIN
FREQ
SS
Main Power Supply Input. VIN powers the ADP1612/ADP1613 internal circuitry. Connect VIN to the input source
voltage. Bypass VIN to GND with a 10 μF or greater capacitor as close to the ADP1612/ADP1613 as possible.
Frequency Setting Input. FREQ controls the switching frequency. Connect FREQ to GND to program the oscillator
to 650 kHz, or connect FREQ to VIN to program it to 1.3 MHz. If FREQ is left floating, the part defaults to 650 kHz.
Soft Start Timing Capacitor Input. A capacitor connected from SS to GND brings up the output slowly at power-
up and reduces inrush current.
Rev. A | Page 5 of 28
ADP1612/ADP1613
TYPICAL PERFORMANCE CHARACTERISTICS
VEN = VIN and TA = 25°C, unless otherwise noted.
100
100
90
ADP1612
ADP1612
V
= 3.3V
V
= 5V
IN
IN
fSW = 650kHz
= 25°C
fSW = 1.3MHz
T = 25°C
A
90
80
70
T
A
80
70
60
50
40
60
50
40
V
V
V
= 5V
= 12V
= 15V
OUT
OUT
OUT
V
V
= 12V
= 15V
OUT
OUT
30
30
1
10
100
1k
1
10
100
1k
LOAD CURRENT (mA)
LOAD CURRENT (mA)
Figure 4. ADP1612 Efficiency vs. Load Current, VIN = 3.3 V, fSW = 650 kHz
Figure 7. ADP1612 Efficiency vs. Load Current, VIN = 5 V, fSW = 1.3 MHz
100
100
ADP1612
ADP1613
V
= 3.3V
V
= 5V
IN
IN
fSW = 1.3MHz
= 25°C
fSW = 650kHz
T = 25°C
A
90
80
70
90
80
70
T
A
60
50
40
60
50
40
V
V
V
= 5V
= 12V
= 15V
V
V
V
= 12V
= 15V
= 20V
OUT
OUT
OUT
OUT
OUT
OUT
30
30
1
10
100
1k
1
10
100
1k
LOAD CURRENT (mA)
LOAD CURRENT (mA)
Figure 5. ADP1612 Efficiency vs. Load Current, VIN = 3.3 V, fSW = 1.3 MHz
Figure 8. ADP1613 Efficiency vs. Load Current, VIN = 5 V, fSW = 650 kHz
100
100
ADP1612
ADP1613
V
= 5V
V
= 5V
IN
IN
fSW = 650kHz
= 25°C
fSW = 1.3MHz
T = 25°C
A
90
80
70
90
80
70
T
A
60
50
40
60
50
40
V
V
V
= 12V
= 15V
= 20V
OUT
OUT
OUT
V
V
= 12V
= 15V
OUT
OUT
30
30
1
10
100
1k
1
10
100
1k
LOAD CURRENT (mA)
LOAD CURRENT (mA)
Figure 6. ADP1612 Efficiency vs. Load Current, VIN = 5 V, fSW = 650 kHz
Figure 9. ADP1613 Efficiency vs. Load Current, VIN = 5 V, fSW = 1.3 MHz
Rev. A | Page 6 of 28
ADP1612/ADP1613
2.4
2.2
2.0
1.8
3.4
3.2
3.0
ADP1613
ADP1612
T
= +25°C
A
T
= +25°C
A
2.8
2.6
2.4
2.2
T
= –40°C
1.6
1.4
1.2
A
T
= –40°C
A
T
= +85°C
2.8
T
= +85°C
A
A
2.0
2.5
1.8
2.3
3.3
3.8
4.3
4.8
3.0
3.5
4.0
4.5
INPUT VOLTAGE (V)
INPUT VOLTAGE (V)
Figure 10. ADP1612 Switch Current Limit vs. Input Voltage, VOUT = 5 V
Figure 13. ADP1613 Switch Current Limit vs. Input Voltage, VOUT = 5 V
2.6
2.0
ADP1613
ADP1612
1.8
2.4
T
= +25°C
A
T
= +25°C
A
1.6
2.2
2.0
1.8
1.4
1.2
1.0
T
= –40°C
A
T
= –40°C
A
T
= +85°C
A
T
= +85°C
2.8
A
2.5
3.0
3.5
4.0
4.5
5.0
5.5
1.8
2.3
3.3
3.8
4.3
4.8
5.3
INPUT VOLTAGE (V)
INPUT VOLTAGE (V)
Figure 11. ADP1612 Switch Current Limit vs. Input Voltage, VOUT = 8 V
Figure 14. ADP1613 Switch Current Limit vs. Input Voltage, VOUT = 8 V
1.6
2.6
ADP1613
ADP1612
2.4
1.4
T
= +25°C
A
T
= –40°C
A
T
= –40°C
A
2.2
2.0
1.2
1.0
0.8
1.8
1.6
1.4
T
= +85°C
A
T
= +25°C
A
T
= +85°C
4.0
A
1.8
2.3
2.8
3.3
3.8
4.3
4.8
5.3
2.5
3.0
3.5
4.5
5.0
5.5
INPUT VOLTAGE (V)
INPUT VOLTAGE (V)
Figure 12. ADP1612 Switch Current Limit vs. Input Voltage, VOUT = 15 V
Figure 15. ADP1613 Switch Current Limit vs. Input Voltage, VOUT = 15 V
Rev. A | Page 7 of 28
ADP1612/ADP1613
800
750
700
6
5
4
ADP1612/ADP1613
ADP1612/ADP1613
T
= +25°C
A
T
= +125°C
A
650
600
550
500
450
400
T
= +125°C
A
T
= –40°C
A
3
2
1
T
= –40°C
A
T
= +25°C
A
1.8
2.3
2.8
3.3
3.8
4.3
4.8
5.3
1.8
2.3
2.8
3.3
3.8
4.3
4.8
5.3
INPUT VOLTAGE (V)
INPUT VOLTAGE (V)
Figure 16. ADP1612/ADP1613 Quiescent Current vs. Input Voltage,
Nonswitching, fSW = 650 kHz
Figure 19. ADP1612/ADP1613 Quiescent Current vs. Input Voltage, Switching,
fSW = 1.3 MHz
800
250
I
= 1A
SW
ADP1612/ADP1613
ADP1612/ADP1613
230
210
750
700
T
= +30°C
A
190
170
150
130
T
= +125°C
T
= +85°C
A
A
650
600
550
500
T
= –40°C
A
110
T
= +25°C
2.8
A
90
70
T
= –40°C
2.3
A
1.8
2.3
3.3
3.8
4.3
4.8
5.3
1.8
2.8
3.3
3.8
4.3
4.8
5.3
INPUT VOLTAGE (V)
INPUT VOLTAGE (V)
Figure 17. ADP1612/ADP1613 Quiescent Current vs. Input Voltage,
Nonswitching, fSW = 1.3 MHz
Figure 20. ADP1612/ADP1613 On Resistance vs. Input Voltage
3.5
250
I
= 1A
SW
ADP1612/ADP1613
ADP1612/ADP1613
230
210
V
= 1.8V
IN
V
3.0
T
= +25°C
A
190
170
150
130
2.5
= 2.5V
T
= +125°C
IN
A
2.0
1.5
1.0
T
= –40°C
A
110
V
= 3.6V
IN
90
70
V
= 5.5V
IN
1.8
2.3
2.8
3.3
3.8
4.3
4.8
5.3
–40
–15
10
35
60
85
INPUT VOLTAGE (V)
TEMPERATURE (°C)
Figure 18. ADP1612/ADP1613 Quiescent Current vs. Input Voltage, Switching,
fSW = 650 kHz
Figure 21. ADP1612/ADP1613 On Resistance vs. Temperature
Rev. A | Page 8 of 28
ADP1612/ADP1613
660
650
640
630
620
610
600
590
580
5.1
5.0
4.9
4.8
4.7
4.6
4.5
ADP1612/ADP1613
ADP1612/ADP1613
T
= +25°C
V
= 1.8V
IN
A
V
= 5.5V
IN
T
= +125°C
A
V
= 3.6V
IN
T
= –40°C
2.8
A
1.8
2.3
3.3
3.8
4.3
4.8
5.3
–40
–10
20
50
80
110
INPUT VOLTAGE (V)
TEMPERATURE (°C)
Figure 22. ADP1612/ADP1613 Frequency vs. Input Voltage, fSW = 650 kHz
Figure 25. ADP1612/ADP1613 SS Pin Current vs. Temperature
1.32
92.8
ADP1612/ADP1613
ADP1612/ADP1613
T
= +25°C
1.30
1.28
A
92.6
T
= +25°C
A
T
= +125°C
92.4
92.2
92.0
91.8
91.6
91.4
91.2
A
1.26
1.24
1.22
1.20
T
= –40°C
A
T
= –40°C
A
1.18
T
= +125°C
A
1.16
1.14
1.8
2.3
2.8
3.3
3.8
4.3
4.8
5.3
1.8
2.3
2.8
3.3
3.8
4.3
4.8
5.3
INPUT VOLTAGE (V)
INPUT VOLTAGE (V)
Figure 23. ADP1612/ADP1613 Frequency vs. Input Voltage, fSW = 1.3 MHz
Figure 26. ADP1612/ADP1613 Maximum Duty Cycle vs. Input Voltage,
fSW = 650 kHz
93.4
7
ADP1612/ADP1613
T
= +125°C
ADP1612/ADP1613
A
93.2
93.0
6
T
= +25°C
A
T
= +125°C
A
5
4
92.8
92.6
92.4
92.2
T
= –40°C
A
3
2
1
T
= +25°C
A
92.0
T
= –40°C
91.8
91.6
A
0
1.8
2.3
2.8
3.3
3.8
4.3
4.8
5.3
0
0.5 1.0 1.5 2.0 2.5 3.0 3.5 4.0 4.5 5.0 5.5
EN PIN VOLTAGE (V)
INPUT VOLTAGE (V)
Figure 24. ADP1612/ADP1613 EN Pin Current vs. EN Pin Voltage
Figure 27. ADP1612/ADP1613 Maximum Duty Cycle vs. Input Voltage,
fSW = 1.3 MHz
Rev. A | Page 9 of 28
ADP1612/ADP1613
T
T
OUTPUT VOLTAGE (5V/DIV)
OUTPUT VOLTAGE (5V/DIV)
V
V
I
= 5V
= 12V
IN
OUT
= 250mA
V
V
I
= 5V
= 12V
LOAD
IN
OUT
L = 6.8µH
f
= 1.3MHz
= 20mA
SW
LOAD
SWITCH VOLTAGE (10V/DIV)
L = 6.8µH
= 1.3MHz
INDUCTOR CURRENT
(200mA/DIV)
f
SW
C
= 10µF
OUT
INDUCTOR CURRENT (2A/DIV)
EN PIN VOLTAGE (5V/DIV)
SWITCH VOLTAGE (10V/DIV)
TIME (400ns/DIV)
TIME (20ms/DIV)
Figure 28. ADP1612/ADP1613 Switching Waveform in Discontinuous
Conduction Mode
Figure 31. ADP1612/ADP1613 Start-Up from VIN, CSS =100 nF
T
T
OUTPUT VOLTAGE (5V/DIV)
OUTPUT VOLTAGE (5V/DIV)
V
V
= 5V
IN
= 12V
OUT
I
= 200mA
LOAD
L = 6.8µH
SWITCH VOLTAGE (10V/DIV)
f
= 1.3MHz
SW
INDUCTOR CURRENT
(500mA/DIV)
C
= 10µF
OUT
V
V
= 5V
IN
= 12V
OUT
I
= 250mA
LOAD
L = 6.8µH
f
= 1.3MHz
SW
SWITCH VOLTAGE (10V/DIV)
INDUCTOR CURRENT (500mA/DIV)
EN PIN VOLTAGE (5V/DIV)
TIME (400µs/DIV)
TIME (400ns/DIV)
Figure 29. ADP1612/ADP1613 Switching Waveform in Continuous
Conduction Mode
Figure 32. ADP1612/ADP1613 Start-Up from Shutdown, CSS = 33 nF
T
T
OUTPUT VOLTAGE (5V/DIV)
V
V
= 5V
IN
= 12V
OUT
I
= 250mA
LOAD
OUTPUT VOLTAGE (5V/DIV)
L = 6.8µH
f
= 1.3MHz
SW
SWITCH VOLTAGE (10V/DIV)
V
V
= 5V
IN
= 12V
OUT
SWITCH VOLTAGE (10V/DIV)
I
= 250mA
LOAD
L = 6.8µH
f
= 1.3MHz
SW
INDUCTOR CURRENT (500mA/DIV)
INDUCTOR CURRENT (2A/DIV)
EN PIN VOLTAGE (5V/DIV)
TIME (20ms/DIV)
EN PIN VOLTAGE (5V/DIV)
TIME (400µs/DIV)
Figure 30. ADP1612/ADP1613 Start-Up from VIN, CSS =33 nF
Figure 33. ADP1612/ADP1613 Start-Up from Shutdown, CSS = 100 nF
Rev. A | Page 10 of 28
ADP1612/ADP1613
THEORY OF OPERATION
L1
V
IN
>1.6V
<0.3V
C
IN
VIN
FREQ
6
7
D1
+
SW
V
5
OUT
V
A
IN
D
C
+
OUT
COMPARATOR
CURRENT
SENSING
V
OUT
PWM
COMPARATOR
D
REF
ERROR
R1
R2
AMPLIFIER
FB
2
1
OSCILLATOR
5µA
V
BG
UVLO
COMPARATOR
DRIVER
COMP
V
IN
S
R
Q
N1
R
UVLO
COMP
REF
V
SS
TSD
COMPARATOR
C
COMP
5µA
T
SENSE
BAND GAP
BG
SS
SOFT
START
RESET
T
REF
8
C
SS
AGND
1.1MΩ
AGND
ADP1612/AD1613
3
4
EN
GND
>1.6V
<0.3V
Figure 34. Block Diagram with Step-Up Regulator Application Circuit
The ADP1612/ADP1613 current-mode step-up switching
converters boost a 1.8 V to 5.5 V input voltage to an output
voltage as high as 20 V. The internal switch allows a high
output current, and the high 650 kHz/1.3 MHz switching
frequency allows for the use of tiny external components.
The switch current is monitored on a pulse-by-pulse basis to
limit it to 1.4 A typical (ADP1612) or 2.0 A typical (ADP1613).
FREQUENCY SELECTION
The frequency of the ADP1612/ADP1613 is pin-selectable
to operate at either 650 kHz to optimize the regulator for high
efficiency or at 1.3 MHz for use with small external components.
If FREQ is left floating, the part defaults to 650 kHz. Connect
FREQ to GND for 650 kHz operation or connect FREQ to VIN
for 1.3 MHz operation. When connected to VIN for 1.3 MHz
operation, an additional 5 μA, typical, of quiescent current is
active. This current is turned off when the part is shutdown.
CURRENT-MODE PWM OPERATION
The ADP1612/ADP1613 utilize a current-mode PWM control
scheme to regulate the output voltage over all load conditions.
The output voltage is monitored at FB through a resistive voltage
divider. The voltage at FB is compared to the internal 1.235 V
reference by the internal transconductance error amplifier to
create an error voltage at COMP. The switch current is internally
measured and added to the stabilizing ramp. The resulting sum
is compared to the error voltage at COMP to control the PWM
modulator. This current-mode regulation system allows fast
transient response, while maintaining a stable output voltage.
By selecting the proper resistor-capacitor network from COMP
to GND, the regulator response is optimized for a wide range of
input voltages, output voltages, and load conditions.
SOFT START
To prevent input inrush current to the converter when the part is
enabled, connect a capacitor from SS to GND to set the soft start
period. Once the ADP1612/ADP1613 are turned on, SS sources
5 ꢀA, typical, to the soft start capacitor (CSS) until it reaches
1.2 V at startup. As the soft start capacitor charges, it limits the
peak current allowed by the part. By slowly charging the soft
start capacitor, the input current ramps slowly to prevent it
from overshooting excessively at startup. When the ADP1612/
ADP1613 are in shutdown mode (EN ≤ 0.3 V), a thermal shut-
down event occurs, or the input voltage is below the falling
undervoltage lockout voltage, SS is internally shorted to GND
to discharge the soft start capacitor.
Rev. A | Page 11 of 28
ADP1612/ADP1613
THERMAL SHUTDOWN (TSD)
ENABLE/SHUTDOWN CONTROL
The ADP1612/ADP1613 include TSD protection. If the die
temperature exceeds 150°C (typical), TSD turns off the NMOS
power device, significantly reducing power dissipation in the
device and preventing output voltage regulation. The NMOS
power device remains off until the die temperature reduces to
130°C (typical). The soft start capacitor is discharged during
TSD to ensure low output voltage overshoot and inrush
currents when regulation resumes.
The EN input turns the ADP1612/ADP1613 regulator on or
off. Drive EN low to turn off the regulator and reduce the
input current to 0.01 ꢀA, typical. Drive EN high to turn on
the regulator.
When the step-up dc-to-dc switching converter is in shutdown
mode (EN ≤ 0.3 V), there is a dc path from the input to the output
through the inductor and output rectifier. This causes the output
voltage to remain slightly below the input voltage by the forward
voltage of the rectifier, preventing the output voltage from dropping
to ground when the regulator is shutdown. Figure 37 provides a
circuit modification to disconnect the output voltage from the
input voltage at shutdown.
UNDERVOLTAGE LOCKOUT (UVLO)
If the input voltage is below the UVLO threshold, the ADP1612/
ADP1613 automatically turn off the power switch and place
the part into a low power consumption mode. This prevents
potentially erratic operation at low input voltages and prevents
the power device from turning on when the control circuitry
cannot operate it. The UVLO levels have ~100 mV of hysteresis
to ensure glitch free startup.
Regardless of the state of the EN pin, when a voltage is applied to
VIN of the ADP1612/ADP1613, a large current spike occurs due
to the nonisolated path through the inductor and diode between
VIN and VOUT. The high current is a result of the output capacitor
charging. The peak value is dependent on the inductor, output
capacitor, and any load active on the output of the regulator.
Rev. A | Page 12 of 28
ADP1612/ADP1613
APPLICATIONS INFORMATION
For CCM duty cycles greater than 50% that occur with input
voltages less than one-half the output voltage, slope compen-
sation is required to maintain stability of the current-mode
regulator. For stable current-mode operation, ensure that the
selected inductance is equal to or greater than the minimum
calculated inductance, LMIN, for the application parameters in
the following equation:
SETTING THE OUTPUT VOLTAGE
The ADP1612/ADP1613 feature an adjustable output voltage
range of VIN to 20 V. The output voltage is set by the resistor
voltage divider, R1 and R2, (see Figure 34) from the output
voltage (VOUT) to the 1.235 V feedback input at FB. Use the
following equation to determine the output voltage:
V
OUT = 1.235 × (1 + R1/R2)
(1)
(2)
(VOUT − 2 ×VIN )
Choose R1 based on the following equation:
L > LMIN
=
(7)
2.7 × fSW
V
−1.235
⎛
⎜
⎞
⎟
OUT
R1= R2 ×
Inductors smaller than the 4.7 ꢀH to 22 ꢀH recommended
1.235
⎝
⎠
range can be used as long as Equation 7 is satisfied for the given
application. For input/output combinations that approach the
90% maximum duty cycle, doubling the inductor is recom-
mended to ensure stable operation. Table 5 suggests a series
of inductors for use with the ADP1612/ADP1613.
INDUCTOR SELECTION
The inductor is an essential part of the step-up switching
converter. It stores energy during the on time of the power
switch, and transfers that energy to the output through the
output rectifier during the off time. To balance the tradeoffs
between small inductor current ripple and efficiency, induc-
tance values in the range of 4.7 ꢀH to 22 ꢀH are recommended.
In general, lower inductance values have higher saturation
current and lower series resistance for a given physical size.
However, lower inductance results in a higher peak current
that can lead to reduced efficiency and greater input and/or
output ripple and noise. A peak-to-peak inductor ripple current
close to 30% of the maximum dc input current typically yields
an optimal compromise.
Table 5. Suggested Inductors
Dimensions
Manufacturer
Part Series
CMD4D11
CDRH4D28CNP
CDRH5D18NP
CDRH6D26HPNP
DO3308P
L × W × H (mm)
5.8 × 4.4 × 1.2
5.1 × 5.1 × 3.0
6.0 × 6.0 × 2.0
7.0 × 7.0 × 2.8
12.95 × 9.4 × 3.0
12.95 × 9.4 × 5.21
5.2 × 5.2 × 2.0
6.2 × 6.3 × 2.0
6.2 × 6.3 × 3.5
Assorted
Sumida
Coilcraft
Toko
DO3316P
D52LC
D62LCB
D63LCB
For determining the inductor ripple current in continuous
operation, the input (VIN) and output (VOUT) voltages determine
the switch duty cycle (D) by the following equation:
Würth
WE-TPC
VOUT − VIN
Elektronik
WE-PD, PD2, PD3, PD4
Assorted
D =
(3)
VOUT
CHOOSING THE INPUT AND OUTPUT CAPACITORS
Using the duty cycle and switching frequency, fSW, determine
the on time by the following equation:
The ADP1612/ADP1613 require input and output bypass capa-
citors to supply transient currents while maintaining constant
input and output voltages. Use a low equivalent series resistance
(ESR), 10 ꢀF or greater input capacitor to prevent noise at the
ADP1612/ADP1613 input. Place the capacitor between VIN
and GND as close to the ADP1612/ADP1613 as possible.
Ceramic capacitors are preferred because of their low ESR
characteristics. Alternatively, use a high value, medium ESR
capacitor in parallel with a 0.1 ꢀF low ESR capacitor as close
to the ADP1612/ADP1613 as possible.
D
fSW
tON
=
(4)
The inductor ripple current (ΔIL) in steady state is calculated by
V
IN ×tON
L
ΔIL =
(5)
(6)
Solve for the inductance value (L) by the following equation:
VIN × tON
L =
ΔIL
Ensure that the peak inductor current (the maximum input
current plus half the inductor ripple current) is below the rated
saturation current of the inductor. Likewise, make sure that the
maximum rated rms current of the inductor is greater than the
maximum dc input current to the regulator.
Rev. A | Page 13 of 28
ADP1612/ADP1613
The output capacitor maintains the output voltage and supplies
current to the load while the ADP1612/ADP1613 switch is on.
The value and characteristics of the output capacitor greatly
affect the output voltage ripple and stability of the regulator. A
low ESR ceramic dielectric capacitor is preferred. The output
voltage ripple (ΔVOUT) is calculated as follows:
LOOP COMPENSATION
The ADP1612/ADP1613 use external components to
compensate the regulator loop, allowing optimization of
the loop dynamics for a given application.
The step-up converter produces an undesirable right-half plane
zero in the regulation feedback loop. This requires compensating
the regulator such that the crossover frequency occurs well
below the frequency of the right-half plane zero. The right-
half plane zero is determined by the following equation:
QC
COUT
IL ×tON
COUT
ΔVOUT
=
=
(8)
where:
QC is the charge removed from the capacitor.
ON is the on time of the switch.
OUT is the output capacitance.
2
⎛
⎜
⎜
⎝
⎞
⎟
⎟
⎠
VIN
VOUT
RLOAD
2π× L
FZ (RHP) =
×
(13)
t
C
IL is the average inductor current.
where:
FZ(RHP) is the right-half plane zero.
LOAD is the equivalent load resistance or the output voltage
D
fSW
tON
=
(9)
R
divided by the load current.
and
To stabilize the regulator, ensure that the regulator crossover
frequency is less than or equal to one-fifth of the right-half
plane zero.
VOUT −VIN
D =
(10)
VOUT
The regulator loop gain is
Choose the output capacitor based on the following equation:
VFB
VIN
VOUT VOUT
IL ×(VOUT −VIN )
fSW ×VOUT × ΔVOUT
AVL
=
×
×GMEA × ZCOMP ×GCS × ZOUT
(14)
COUT
≥
(11)
where:
VL is the loop gain.
VFB is the feedback regulation voltage, 1.235 V.
OUT is the regulated output voltage.
VIN is the input voltage.
MEA is the error amplifier transconductance gain.
COMP is the impedance of the series RC network from COMP
Multilayer ceramic capacitors are recommended for this
application.
A
DIODE SELECTION
V
The output rectifier conducts the inductor current to the output
capacitor and load while the switch is off. For high efficiency,
minimize the forward voltage drop of the diode. For this reason,
Schottky rectifiers are recommended. However, for high voltage,
high temperature applications, where the Schottky rectifier
reverse leakage current becomes significant and can degrade
efficiency, use an ultrafast junction diode.
G
Z
to GND.
GCS is the current sense transconductance gain (the inductor
current divided by the voltage at COMP), which is internally
set by the ADP1612/ADP1613.
ZOUT is the impedance of the load and output capacitor.
Ensure that the diode is rated to handle the average output
load current. Many diode manufacturers derate the current
capability of the diode as a function of the duty cycle. Verify
that the output diode is rated to handle the average output
load current with the minimum duty cycle. The minimum
duty cycle of the ADP1612/ADP1613 is
VOUT −VIN(MAX)
DMIN
=
(12)
VOUT
where VIN(MAX) is the maximum input voltage.
The following are suggested Schottky diode manufacturers:
•
•
ON Semiconductor
Diodes, Inc.
Rev. A | Page 14 of 28
ADP1612/ADP1613
To determine the crossover frequency, it is important to note
that, at that frequency, the compensation impedance (ZCOMP
The capacitor, C2, is chosen to cancel the zero introduced by
output capacitance, ESR.
)
is dominated by a resistor, and the output impedance (ZOUT) is
dominated by the impedance of an output capacitor. Therefore,
when solving for the crossover frequency, the equation (by
definition of the crossover frequency) is simplified to
Solve for C2 as follows:
ESR ×COUT
C2 =
(19)
RCOMP
For low ESR output capacitance such as with a ceramic
capacitor, C2 is optional. For optimal transient performance,
COMP and CCOMP might need to be adjusted by observing the
VFB
VIN
VOUT VOUT
AVL
=
×
×GMEA × RCOMP ×GCS ×
(15)
R
1
=1
load transient response of the ADP1612/ADP1613. For most
applications, the compensation resistor should be within the
range of 4.7 kΩ to 100 kΩ and the compensation capacitor
should be within the range of 100 pF to 3.3 nF.
2π× fC ×COUT
where:
fC is the crossover frequency.
COMP is the compensation resistor.
Solve for RCOMP
2π× fC ×COUT ×(VOUT
R
SOFT START CAPACITOR
,
Upon startup (EN ≥ 1.6 V), the voltage at SS ramps up slowly
by charging the soft start capacitor (CSS) with an internal 5 ꢀA
current source (ISS). As the soft start capacitor charges, it limits
the peak current allowed by the part to prevent excessive over-
shoot at startup. The necessary soft start capacitor, CSS, for a
specific overshoot and start-up time can be calculated for the
maximum load condition when the part is at current limit by:
2
)
RCOMP
=
(16)
(17)
V
FB ×VIN ×GMEA ×GCS
where:
VFB = 1.235 V.
MEA = 80 ꢀA/V.
GCS = 13.4 A/V.
G
Δt
VSS
CSS = ISS
(20)
2
4746 × fC ×COUT ×(VOUT
)
RCOMP
=
VIN
where:
Once the compensation resistor is known, set the zero formed
by the compensation capacitor and resistor to one-fourth of the
crossover frequency, or
ISS = 5 μA (typical).
VSS = 1.2 V.
Δt = startup time, at current limit.
2
If the applied load does not place the part at current limit, the
necessary CSS will be smaller. A 33 nF soft start capacitor results
in negligible input current overshoot at start up, and therefore is
suitable for most applications. However, if an unusually large
output capacitor is used, a longer soft start period is required
to prevent input inrush current.
CCOMP
=
(18)
π× fC × RCOMP
where CCOMP is the compensation capacitor.
ERROR
AMPLIFIER
COMP
1
2
FB
g
m
Conversely, if fast startup is a requirement, the soft start
capacitor can be reduced or removed, allowing the
ADP1612/ADP1613 to start quickly, but allowing greater
peak switch current.
V
BG
R
COMP
C2
C
COMP
Figure 35. Compensation Components
Rev. A | Page 15 of 28
ADP1612/ADP1613
TYPICAL APPLICATION CIRCUITS
Both the ADP1612 and ADP1613 can be used in the application
circuits in this section.
STEP-UP REGULATOR CIRCUIT EXAMPLES
ADP1612 Step-Up Regulator
The ADP1612 is geared toward applications requiring input
voltages as low as 1.8 V, where the ADP1613 is more suited for
applications needing the output power capabilities of a 2.0 A
switch. The primary differences are shown in Table 6.
L1
4.7µH
D1
3A, 40V
V
= 1.8V TO 4.2V
V
= 5V
IN
OUT
6
3
7
8
5
VIN
SW
ON
ADP1612
R1
30kΩ
OFF
EN
Table 6. ADP1612/ADP1613 Differences
C
IN
2
1
FB
10µF
C
OUT
10µF
Parameter
ADP1612
ADP1613
2.0 A
FREQ
SS
R2
10kΩ
Current Limit
1.4 A
COMP
R
COMP
6.8kΩ
Input Voltage Range
1.8 V to 5.5 V
2.5 V to 5.5 V
C
GND
SS
33nF
C
COMP
3300pF
4
The Step-Up Regulator Circuit Examples section recommends
component values for several common input, output, and load
conditions. The equations in the Applications Information
section can be used to select components for alternate
configurations.
L1: DO3316P-472ML
D1: MBRA340T3G
R1: RC0805FR-0730KL
R2: CRCW080510K0FKEA
C
C
C
C
: ECJ-2VB1H332K
COMP
: GRM21BR61C106KE15L
: GRM32DR71E106KA12L
IN
OUT
R
: RC0805JR-076K8L
: ECJ-2VB1H333K
SS
COMP
Figure 38. ADP1612 Step-Up Regulator Configuration
VOUT = 5 V, fSW = 650 kHz
STEP-UP REGULATOR
The circuit in Figure 36 shows the ADP1612/ADP1613 in a
basic step-up configuration.
100
90
ADP1612
V
= 5V
OUT
fSW = 650kHz
= 25°C
L1
T
A
ADP1612/
ADP1613
80
D1
V
V
OUT
IN
6
3
7
8
5
2
1
VIN
EN
SW
FB
70
ON
R1
R2
OFF
60
50
40
C
IN
1.3MHz
650kHz
(DEFAULT)
FREQ
SS
V
V
V
V
= 1.8V
= 2.7V
= 3.3V
= 4.2V
IN
IN
IN
IN
COMP
C
OUT
GND
4
R
COMP
C
SS
C
COMP
30
1
10
100
1k
10k
LOAD CURRENT (mA)
Figure 36. Step-Up Regulator
Figure 39. ADP1612 Efficiency vs. Load Current
VOUT = 5 V, fSW = 650 kHz
The modified step-up circuit in Figure 37 incorporates true
shutdown capability advantageous for battery-powered applica-
tions requiring low standby current. Driving the EN pin below
0.3 V shuts down the ADP1612/ADP1613 and completely
disconnects the input from the output.
T
V
f
= 5V
OUT
= 650kHz
SW
OUTPUT VOLTAGE (50mV/DIV)
AC-COUPLED
L1
NTGD1100L
ADP1612/
Q1
D1
ADP1613
V
V
OUT
IN
A
6
3
7
8
5
2
1
LOAD CURRENT (50mA/DIV)
VIN
SW
R3
10kΩ
R1
R2
EN
C
IN
FB
1.3MHz
Q1
B
650kHz
(DEFAULT)
FREQ
SS
COMP
C
OUT
GND
R
ON
COMP
C
SS
4
OFF
TIME (100µs/DIV)
C
COMP
Figure 40. ADP1612 50 mA to 150 mA Load Transient (VIN = 3.3 V)
VOUT = 5 V, fSW = 650 kHz
Figure 37. Step-Up Regulator with True Shutdown
Rev. A | Page 16 of 28
ADP1612/ADP1613
L1
L1
4.7µH
10µH
D1
3A, 40V
D1
2A, 20V
V
= 1.8V TO 4.2V
V
= 5V
V
= 2.7V TO 5V
V
= 12V
IN
OUT
IN
OUT
6
3
7
8
5
6
3
7
8
5
VIN
SW
VIN
SW
ON
ADP1612
EN
R1
30kΩ
ON
ADP1612
EN
R1
86.6kΩ
OFF
OFF
C
C
IN
IN
10µF
2
1
FB
2
1
FB
10µF
C
C
OUT
10µF
OUT
10µF
FREQ
SS
R2
10kΩ
FREQ
SS
R2
10kΩ
COMP
COMP
R
R
COMP
12kΩ
COMP
22kΩ
C
GND
C
GND
SS
33nF
SS
33nF
C
C
COMP
1200pF
COMP
1800pF
4
4
L1: DO3316P-472ML
D1: MBRA340T3G
R1: RC0805FR-0730KL
R2: CRCW080510K0FKEA
L1: DO3316P-103ML
D1: DFLS220L-7
R1: ERJ-6ENF8662V
R2: CRCW080510K0FKEA
C
: ECJ-2VB1H122K
: GRM21BR61C106KE15L
: GRM32DR71E106KA12L
C
: ECJ-2VB1H182K
: GRM21BR61C106KE15L
: GRM32DR71E106KA12L
COMP
COMP
C
C
C
C
C
C
IN
IN
OUT
OUT
R
: RC0805JR-0712KL
: ECJ-2VB1H333K
SS
R
: RC0805JR-0722KL
: ECJ-2VB1H333K
SS
COMP
COMP
Figure 41. ADP1612 Step-Up Regulator Configuration
VOUT = 5 V, fSW = 1.3 MHz
Figure 44. ADP1612 Step-Up Regulator Configuration
VOUT = 12 V, fSW = 650 kHz
100
90
100
ADP1612
ADP1612
V
= 5V
V
= 12V
OUT
OUT
fSW = 1.3MHz
= 25°C
fSW = 650kHz
= 25°C
T
T
A
90
A
80
80
70
70
60
50
40
60
V
= 2.7V
= 3.3V
= 4.2V
= 5.0V
V
V
V
V
= 1.8V
IN
= 2.7V
IN
= 3.3V
IN
= 4.2V
IN
IN
IN
IN
IN
V
V
V
50
40
30
1
10
100
1k
10k
1
10
100
1k
LOAD CURRENT (mA)
LOAD CURRENT (mA)
Figure 42. ADP1612 Efficiency vs. Load Current
VOUT = 5 V, fSW = 1.3 MHz
Figure 45. ADP1612 Efficiency vs. Load Current
VOUT = 12 V, fSW = 650 kHz
T
T
V
f
= 12V
V
f
= 5V
OUT
= 650kHz
OUT
= 1.3MHz
SW
SW
OUTPUT VOLTAGE (50mV/DIV)
AC-COUPLED
OUTPUT VOLTAGE (100mV/DIV)
AC-COUPLED
LOAD CURRENT (50mA/DIV)
LOAD CURRENT (50mA/DIV)
TIME (100µs/DIV)
TIME (100µs/DIV)
Figure 43. ADP1612 50 mA to 150 mA Load Transient (VIN = 3.3 V)
VOUT = 5 V, fSW = 1.3 MHz
Figure 46. ADP1612 50 mA to 150 mA Load Transient (VIN = 3.3 V)
VOUT = 12 V, fSW = 650 kHz
Rev. A | Page 17 of 28
ADP1612/ADP1613
L1
6.8µH
L1
15µH
D1
D1
2A, 20V
2A, 20V
V
= 2.7V TO 5V
V
= 12V
V
= 2.7V TO 5V
V
= 15V
IN
OUT
IN
OUT
6
3
7
8
5
6
3
7
8
5
VIN
SW
VIN
SW
ON
ADP1612
EN
R1
86.6kΩ
ON
ADP1612
EN
R1
110kΩ
OFF
OFF
C
C
IN
10µF
IN
10µF
2
1
2
1
FB
FB
C
C
OUT
10µF
OUT
10µF
FREQ
SS
FREQ
SS
R2
10kΩ
R2
10kΩ
COMP
COMP
R
R
COMP
18kΩ
COMP
22kΩ
C
C
GND
GND
SS
33nF
SS
33nF
C
C
COMP
680pF
COMP
1800pF
4
4
L1: DO3316P-682ML
D1: DFLS220L-7
R1: ERJ-6ENF8662V
R2: CRCW080510K0FKEA
L1: DO3316P-153ML
D1: DFLS220L-7
R1: ERJ-6ENF1103V
R2: CRCW080510K0FKEA
C
C
C
C
: CC0805KRX7R9BB681
: GRM21BR61C106KE15L
: GRM32DR71E106KA12L
C
C
C
C
: ECJ-2VB1H182K
: GRM21BR61C106KE15L
: GRM32DR71E106KA12L
OUT
COMP
COMP
IN
IN
OUT
R
: RC0805JR-0718KL
: ECJ-2VB1H333K
R
: RC0805JR-0722KL
: ECJ-2VB1H333K
SS
COMP
SS
COMP
Figure 47. ADP1612 Step-Up Regulator Configuration
VOUT = 12 V, fSW = 1.3 MHz
Figure 50. ADP1612 Step-Up Regulator Configuration
VOUT = 15 V, fSW = 650 kHz
100
100
ADP1612
ADP1612
V
= 12V
V
= 15V
OUT
OUT
fSW = 1.3MHz
= 25°C
fSW = 650kHz
= 25°C
90
80
70
T
T
A
90
A
80
70
60
50
40
60
V
V
V
V
= 2.7V
= 3.3V
= 4.2V
= 5.0V
V
V
V
V
= 2.7V
= 3.3V
= 4.2V
= 5.0V
IN
IN
IN
IN
IN
IN
IN
IN
50
40
30
1
10
100
1k
1
10
100
1k
LOAD CURRENT (mA)
LOAD CURRENT (mA)
Figure 48. ADP1612 Efficiency vs. Load Current
VOUT = 12 V, fSW = 1.3 MHz
Figure 51. ADP1612 Efficiency vs. Load Current
VOUT = 15 V, fSW = 650 kHz
T
V
f
= 12V
T
V
f
= 15V
OUT
= 1.3MHz
OUT
= 650kHz
SW
SW
OUTPUT VOLTAGE (100mV/DIV)
AC-COUPLED
OUTPUT VOLTAGE (200mV/DIV)
AC-COUPLED
LOAD CURRENT (50mA/DIV)
LOAD CURRENT (50mA/DIV)
TIME (100µs/DIV)
TIME (100µs/DIV)
Figure 49. ADP1612 50 mA to 150 mA Load Transient (VIN = 3.3 V)
VOUT = 12 V, fSW = 1.3 MHz
Figure 52. ADP1612 50 mA to 150 mA Load Transient (VIN = 3.3 V)
VOUT = 15 V, fSW = 650 kHz
Rev. A | Page 18 of 28
ADP1612/ADP1613
ADP1613 Step-Up Regulator
L1
10µH
L1
10µH
D1
D1
2A, 20V
3A, 40V
V
= 2.7V TO 5V
V
= 15V
V
= 2.7V TO 5V
V
= 12V
IN
OUT
IN
OUT
6
3
7
8
5
6
3
7
8
5
VIN
SW
VIN
SW
ON
ADP1612
EN
R1
110kΩ
ON
ADP1613
EN
R1
86.6kΩ
OFF
OFF
C
C
IN
10µF
IN
10µF
2
1
2
1
FB
FB
C
C
OUT
10µF
OUT
10µF
FREQ
SS
FREQ
SS
R2
10kΩ
R2
10kΩ
COMP
COMP
R
R
COMP
10kΩ
COMP
12kΩ
C
C
GND
GND
SS
33nF
SS
33nF
C
C
COMP
1800pF
COMP
2200pF
4
4
L1: DO3316P-103ML
D1: DFLS220L-7
R1: ERJ-6ENF1103V
R2: CRCW080510K0FKEA
L1: DO3316P-103ML
D1: MBRA340T3G
R1: ERJ-6ENF8662V
R2: CRCW080510K0FKEA
C
C
C
C
: ECJ-2VB1H182K
: GRM21BR61C106KE15L
: GRM32DR71E106KA12L
C
C
C
C
: ECJ-2VB1H222K
: GRM21BR61C106KE15L
: GRM32DR71E106KA12L
OUT
COMP
COMP
IN
IN
OUT
R
: RC0805JR-0710KL
: ECJ-2VB1H333K
R
: RC0805JR-0712KL
: ECJ-2VB1H333K
SS
COMP
SS
COMP
Figure 53. ADP1612 Step-Up Regulator Configuration
VOUT =15 V, fSW = 1.3 MHz
Figure 56. ADP1613 Step-Up Regulator Configuration
OUT = 12 V, fSW = 650 kHz
V
100
100
ADP1613
V
= 12V
OUT
ADP1612
V
= 15V
OUT
fSW = 650kHz
= 25°C
fSW = 1.3MHz
= 25°C
90
80
70
90
80
70
60
50
40
30
T
A
T
A
60
50
40
30
V
V
V
V
= 2.7V
= 3.3V
= 4.2V
= 5.0V
IN
IN
IN
IN
V
V
V
V
= 2.7V
= 3.3V
= 4.2V
= 5.0V
IN
IN
IN
IN
1
10
100
1k
1
10
100
1k
LOAD CURRENT (mA)
LOAD CURRENT (mA)
Figure 57. ADP1613 Efficiency vs. Load Current
OUT = 12 V, fSW = 650 kHz
Figure 54. ADP1612 Efficiency vs. Load Current
VOUT =15 V, fSW = 1.3 MHz
V
T
T
V
f
= 12V
V
f
= 15V
OUT
= 650kHz
OUT
= 1.3MHz
SW
SW
OUTPUT VOLTAGE (200mV/DIV)
AC-COUPLED
OUTPUT VOLTAGE (200mV/DIV)
AC-COUPLED
LOAD CURRENT (50mA/DIV)
LOAD CURRENT (50mA/DIV)
TIME (100µs/DIV)
TIME (100µs/DIV)
Figure 55. ADP1612 50 mA to 150 mA Load Transient (VIN = 3.3 V)
VOUT =15 V, fSW = 1.3 MHz
Figure 58. ADP1613 50 mA to 150 mA Load Transient (VIN = 5 V)
VOUT = 12 V, fSW = 650 kHz
Rev. A | Page 19 of 28
ADP1612/ADP1613
L1
6.8µH
L1
15µH
D1
D1
3A, 40V
3A, 40V
V
= 2.7V TO 5V
V
= 12V
V
= 3.3V TO 5.5V
V
= 15V
IN
OUT
IN
OUT
6
3
7
8
5
6
3
7
8
5
VIN
SW
VIN
SW
ON
ADP1613
EN
R1
86.6kΩ
ON
ADP1613
EN
R1
110kΩ
OFF
OFF
C
C
IN
10µF
IN
10µF
2
1
2
1
FB
FB
C
C
OUT
10µF
OUT
10µF
FREQ
SS
FREQ
SS
R2
10kΩ
R2
10kΩ
COMP
COMP
R
R
COMP
10kΩ
COMP
10kΩ
C
C
GND
GND
SS
33nF
SS
33nF
C
C
COMP
1000pF
COMP
1800pF
4
4
L1: DO3316P-682ML
D1: MBRA340T3G
R1: ERJ-6ENF8662V
R2: CRCW080510K0FKEA
L1: DO3316P-153ML
D1: MBRA340T3G
R1: ERJ-6ENF1103V
R2: CRCW080510K0FKEA
C
C
C
C
: ECJ-2VB1H102K
: GRM21BR61C106KE15L
: GRM32DR71E106KA12L
C
C
C
C
: ECJ-2VB1H182K
COMP
COMP
: GRM21BR61C106KE15L
: GRM32DR71E106KA12L
OUT
IN
IN
OUT
R
: RC0805JR-0710KL
: ECJ-2VB1H333K
R
: RC0805JR-0710KL
: ECJ-2VB1H333K
SS
COMP
SS
COMP
Figure 59. ADP1613 Step-Up Regulator Configuration
VOUT = 12 V, fSW = 1.3 MHz
Figure 62. ADP1613 Step-Up Regulator Configuration
VOUT = 15 V, fSW = 650 kHz
100
100
90
ADP1613
ADP1613
V
= 12V
V
= 15V
OUT
OUT
fSW = 1.3MHz
= 25°C
fSW = 650kHz
= 25°C
90
80
70
T
T
A
A
80
70
60
60
50
40
30
50
40
30
V
V
V
V
= 2.7V
= 3.3V
= 4.2V
= 5.0V
V
V
V
V
= 3.3V
= 4.2V
= 5.0V
= 5.5V
IN
IN
IN
IN
IN
IN
IN
IN
1
10
100
1k
1
10
100
1k
LOAD CURRENT (mA)
LOAD CURRENT (mA)
Figure 60. ADP1613 Efficiency vs. Load Current
VOUT = 12 V, fSW = 1.3 MHz
Figure 63. ADP1613 Efficiency vs. Load Current
VOUT = 15 V, fSW = 650 kHz
T
T
V
f
= 12V
V
f
= 15V
OUT
= 1.3MHz
OUT
= 650kHz
SW
SW
OUTPUT VOLTAGE (100mV/DIV)
AC-COUPLED
OUTPUT VOLTAGE (200mV/DIV)
AC-COUPLED
LOAD CURRENT (50mA/DIV)
LOAD CURRENT (50mA/DIV)
TIME (100µs/DIV)
TIME (100µs/DIV)
Figure 61. ADP1613 50 mA to 150 mA Load Transient (VIN = 5 V)
VOUT = 12 V, fSW = 1.3 MHz
Figure 64. ADP1613 50 mA to 150 mA Load Transient (VIN = 5 V)
VOUT = 15 V, fSW = 650 kHz
Rev. A | Page 20 of 28
ADP1612/ADP1613
L1
10µH
L1
15µH
D1
D1
3A, 40V
3A, 40V
V
= 3.3V TO 5.5V
V
= 15V
V
= 3.3V TO 5.5V
V
= 20V
IN
OUT
IN
OUT
6
3
7
8
5
6
3
7
8
5
VIN
SW
VIN
SW
ON
ADP1613
EN
R1
110kΩ
ON
ADP1613
EN
R1
150kΩ
OFF
OFF
C
10µF
C
IN
10µF
IN
2
1
2
1
FB
FB
C
C
OUT
10µF
OUT
10µF
FREQ
SS
FREQ
SS
R2
10kΩ
R2
10kΩ
COMP
COMP
R
R
COMP
8.2kΩ
COMP
18kΩ
C
C
GND
GND
SS
33nF
SS
33nF
C
C
COMP
1200pF
COMP
820pF
4
4
L1: DO3316P-103ML
D1: MBRA340T3G
R1: ERJ-6ENF1103V
R2: CRCW080510K0FKEA
L1: DO3316P-153ML
D1: MBRA340T3G
R1: RC0805JR-07150KL
R2: CRCW080510K0FKEA
C
C
C
C
: ECJ-2VB1H122K
COMP
C
C
C
C
: CC0805KRX7R9BB821
COMP
: GRM21BR61C106KE15L
: GRM32DR71E106KA12L
: GRM21BR61C106KE15L
: GRM32DR71E106KA12L
OUT
IN
IN
OUT
R
: RC0805JR-078K2L
: ECJ-2VB1H333K
R
: RC0805JR-0718KL
: ECJ-2VB1H333K
SS
COMP
SS
COMP
Figure 65. ADP1613 Step-Up Regulator Configuration
VOUT = 15 V, fSW = 1.3 MHz
Figure 68. ADP1613 Step-Up Regulator Configuration
VOUT = 20 V, fSW = 650 kHz
100
90
80
70
60
50
40
30
100
90
ADP1613
ADP1613
V
= 15V
V
= 20V
OUT
OUT
fSW = 1.3MHz
= 25°C
fSW = 650kHz
= 25°C
T
T
A
A
80
70
60
50
40
30
V
V
V
V
= 3.3V
= 4.2V
= 5.0V
= 5.5V
V
V
V
V
= 3.3V
= 4.2V
= 5.0V
= 5.5V
IN
IN
IN
IN
IN
IN
IN
IN
20
1
10
100
1k
1
10
100
1k
LOAD CURRENT (mA)
LOAD CURRENT (mA)
Figure 66. ADP1613 Efficiency vs. Load Current
VOUT = 15 V, fSW = 1.3 MHz
Figure 69. ADP1613 Efficiency vs. Load Current
VOUT = 20 V, fSW = 650 kHz
T
T
V
f
= 15V
V
f
= 20V
OUT
= 1.3MHz
OUT
= 650kHz
SW
SW
OUTPUT VOLTAGE (200mV/DIV)
AC-COUPLED
OUTPUT VOLTAGE (200mV/DIV)
AC-COUPLED
LOAD CURRENT (50mA/DIV)
LOAD CURRENT (50mA/DIV)
TIME (100µs/DIV)
TIME (100µs/DIV)
Figure 67. ADP1613 50 mA to 150 mA Load Transient (VIN = 5 V)
VOUT = 15 V, fSW = 1.3 MHz
Figure 70. ADP1613 50 mA to 150 mA Load Transient (VIN = 5 V)
VOUT = 20 V, fSW = 650 kHz
Rev. A | Page 21 of 28
ADP1612/ADP1613
SEPIC CONVERTER
L1
10µH
The circuit in Figure 74 shows the ADP1612/ADP1613 in a
single-ended primary inductance converter (SEPIC) topology.
This topology is useful for an unregulated input voltage, such as
a battery-powered application in which the input voltage can vary
between 2.7 V to 5 V and the regulated output voltage falls within
the input voltage range.
D1
3A, 40V
V
= 3.3V TO 5.5V
V
= 20V
IN
OUT
6
3
7
8
5
VIN
SW
ON
ADP1613
EN
R1
150kΩ
OFF
C
IN
2
1
FB
10µF
C
OUT
10µF
FREQ
SS
R2
10kΩ
COMP
R
The input and the output are dc isolated by a coupling capacitor
(C1). In steady state, the average voltage of C1 is the input voltage.
When the ADP1612/ADP1613 switch turns on and the diode
turns off, the input voltage provides energy to L1 and C1 provides
energy to L2. When the ADP1612/ADP1613 switch turns off
and the diode turns on, the energy in L1 and L2 is released to
charge the output capacitor (COUT) and the coupling capacitor
(C1) and to supply current to the load.
COMP
8.2kΩ
C
GND
SS
33nF
C
COMP
1200pF
4
L1: DO3316P-103ML
D1: MBRA340T3G
R1: RC0805JR-07150KL
R2: CRCW080510K0FKEA
C
C
C
C
: ECL-2VB1H122K
COMP
: GRM21BR61C106KE15L
: GRM32DR71E106KA12L
IN
OUT
R
: RC0805JR-078K2L
: ECJ-2VB1H333K
SS
COMP
Figure 71. ADP1613 Step-Up Regulator Configuration
VOUT = 20 V, fSW = 1.3 MHz
L1
DO3316P
4.7µH
100
90
80
70
60
50
40
30
ADP1613
V
= 20V
OUT
fSW = 1.3MHz
= 25°C
T
A
ADP1612/
ADP1613
MBRA210LT
2A, 10V
C1
10µF
V
= 2.0V TO 5.5V
V
= 3.3V
OUT
IN
6
3
7
8
5
VIN
EN
SW
ON
L2
OFF
DO3316P
4.7µH
C
IN
10µF
R1
16.9kΩ
FREQ
SS
2
1
FB
R2
10kΩ
COMP
C
OUT
10µF
R
COMP
82kΩ
GND
4
C
SS
C
COMP
220pF
V
V
V
V
= 3.3V
= 4.2V
= 5.0V
= 5.5V
IN
IN
IN
IN
Figure 74. SEPIC Converter
20
1
10
100
1k
TFT LCD BIAS SUPPLY
LOAD CURRENT (mA)
Figure 75 shows a power supply circuit for TFT LCD module
applications. This circuit has +10 V, −5 V, and +22 V outputs.
The +10 V is generated in the step-up configuration. The −5 V
and +22 V are generated by the charge-pump circuit. During
the step-up operation, the SW node switches between +10 V
and ground (neglecting the forward drop of the diode and on
resistance of the switch). When the SW node is high, C5 charges
up to +10 V. When the SW node is low, C5 holds its charge and
forward-biases D8 to charge C6 to −10 V. The Zener diode (D9)
clamps and regulates the output to −5 V.
Figure 72. ADP1613 Efficiency vs. Load Current
VOUT = 20 V, fSW = 1.3 MHz
T
V
f
= 20V
OUT
= 1.3MHz
SW
OUTPUT VOLTAGE (200mV/DIV)
AC-COUPLED
LOAD CURRENT (50mA/DIV)
The VGH output is generated in a similar manner by the charge-
pump capacitors, C1, C2, and C4. The output voltage is tripled
and regulated down to 22 V by the Zener diode, D5.
TIME (100µs/DIV)
Figure 73. ADP1613 50 mA to 150 mA Load Transient (VIN = 5 V)
VOUT = 20 V, fSW = 1.3 MHz
Rev. A | Page 22 of 28
ADP1612/ADP1613
BAV99
D5
R3
200Ω
C4
10nF
VGH
+22V
BAV99
D8
R4
C3
10µF
D5
BZT52C22
C5
10nF
200Ω
VGL
–5V
C6
10µF
D9
D4
BZT52C5VIS
BAV99
D3
D7
C1
10nF
C2
1µF
DO3316P
4.7µH
D2
ADP1612/
ADP1613
D1
V
= 3.3V
V
= 10V
OUT
IN
6
3
7
8
5
2
1
VIN
SW
FB
ON
R1
71.5kΩ
OFF
EN
C
IN
10µF
1.3MHz
650kHz
FREQ
SS
R2
10kΩ
(DEFAULT)
COMP
C
10µF
OUT
GND
4
R
COMP
27kΩ
C
SS
C
COMP
1200pF
Figure 75. TFT LCD Bias Supply
Rev. A | Page 23 of 28
ADP1612/ADP1613
PCB LAYOUT GUIDELINES
For high efficiency, good regulation, and stability, a well-
designed printed circuit board layout is required.
Use the following guidelines when designing printed circuit
boards (also see Figure 34 for a block diagram and Figure 3
for a pin configuration).
•
•
•
Keep the low ESR input capacitor, CIN (labeled as C7 in
Figure 76), close to VIN and GND. This minimizes noise
injected into the part from board parasitic inductance.
Keep the high current path from CIN (labeled as C7 in
Figure 76) through the L1 inductor to SW and GND as
short as possible.
Keep the high current path from VIN through L1, the
rectifier (D1) and the output capacitor, COUT (labeled as
C4 in Figure 76) as short as possible.
•
•
Keep high current traces as short and as wide as possible.
Place the feedback resistors as close to FB as possible to
prevent noise pickup. Connect the ground of the feedback
network directly to an AGND plane that makes a Kelvin
connection to the GND pin.
Figure 76. Example Layout for ADP1612/ADP1613 Boost Application
(Top Layer)
•
•
•
Place the compensation components as close as possible to
COMP. Connect the ground of the compensation network
directly to an AGND plane that makes a Kelvin connection
to the GND pin.
Connect the softstart capacitor, CSS (labeled as C1 in
Figure 76) as close to the device as possible. Connect the
ground of the softstart capacitor to an AGND plane that
makes a Kelvin connection to the GND pin.
Avoid routing high impedance traces from the compensa-
tion and feedback resistors near any node connected to SW
or near the inductor to prevent radiated noise injection.
Figure 77. Example Layout for ADP1612/ADP1613 Boost Application
(Bottom Layer)
Rev. A | Page 24 of 28
ADP1612/ADP1613
OUTLINE DIMENSIONS
3.20
3.00
2.80
8
1
5
4
5.15
4.90
4.65
3.20
3.00
2.80
PIN 1
IDENTIFIER
0.65 BSC
0.95
0.85
0.75
15° MAX
1.10 MAX
0.70
0.55
0.40
0.15
0.05
0.23
0.13
6°
0°
0.40
0.25
COPLANARITY
0.10
COMPLIANT TO JEDEC STANDARDS MO-187-AA
Figure 78. 8-Lead Mini Small Outline Package [MSOP]
(RM-8)
Dimensions shown in millimeters
ORDERING GUIDE
Model
Temperature Range
Package Description
Package Option
RM-8
RM-8
Branding
L7Z
L96
ADP1612ARMZ-R71
ADP1613ARMZ-R71
ADP1612-5-EVALZ1
ADP1612-BL1-EVZ1
ADP1613-12-EVALZ1
ADP1613-BL1-EVZ1
−40°C to +125°C
−40°C to +125°C
8-Lead Mini Small Outline Package [MSOP]
8-Lead Mini Small Outline Package [MSOP]
Evaluation Board, 5 V Output Voltage Configuration
Blank Evaluation Board
Evaluation Board, 12 V Output Voltage Configuration
Blank Evaluation Board
1 Z = RoHS Compliant Part.
Rev. A | Page 25 of 28
ADP1612/ADP1613
NOTES
Rev. A | Page 26 of 28
ADP1612/ADP1613
NOTES
Rev. A | Page 27 of 28
ADP1612/ADP1613
NOTES
©2009 Analog Devices, Inc. All rights reserved. Trademarks and
registered trademarks are the property of their respective owners.
D06772-0-9/09(A)
Rev. A | Page 28 of 28
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