ADP3203 [ADI]
2-Phase IMVP-II & IMVP-III Core Controller for Mobile CPUs; 2相IMVP- II和IMVP -III核心控制器的移动处理器
| 型号： | ADP3203 |
| 厂家： | 
ADI |
| 描述： | 2-Phase IMVP-II & IMVP-III Core Controller for Mobile CPUs |
| 文件： | 总12页 (文件大小：153K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
PRELIMINARY TECHNICAL DATA
2-Phase IMVP-II & IMVP-III
a
Core Controller for Mobile CPUs
Preliminary Technical Data
ADP3203
FEATURES
FUNCTIONAL BLOCK DIAGRAM
Pin Selectable 1 or 2-Phase Operation
Backward Compatible to IMVP-II
Excellent Static and Dynamic Current Sharing
Superior Load Transient Response with ADOPTTM
Optimal Positioning Technology
Noise-Blanking for Speed and Stability
Synchronous Rectifier Control for Extended Battery
Life
Cycle-by-Cycle Current Limiting
Hiccup or Latched Overload Protection
Transient-Glitch-Free Power Good
Soft Start Eliminates Power-On In-Rush Current Surge
Two-Level Over-Voltage and Reverse-Voltage
Protection
VCC
24
ADP3203
1
HYSSET
DSHIFT
HYSTERESIS
SETTING
&
VR
2
3
BSHIFT
SHIFT-MUX
21
OUT2
PHASE
SPLITER
20 OUT1
CS2
23
CLIM
22 CS1
CURRENT
SENSE
MUX
27
CS+
28 CS-
EN
RAMP
25
CORE
APPLICATIONS
26 REG
IMVP II-III Core DC/DC Converters
Fixed Voltage Mobile CPU Core DC/DC Converters
Notebook/Laptop Power Supplies
Programmable Output Power Supplies
4
VID4
5-BIT VID
DAC
&
FIXED
REF
5
6
7
VID3
VID2
DACOUT
18
VID1
VID0
8
VR
GENERAL DESCRIPTION
The ADP3203 is a 1 or 2-phase hysteretic peak current
DC-DC buck converter controller dedicated to power a
mobile processor's core. The optimized low voltage design is
powered from the 3.3 V system supply and draws only
10 µA maximum in shutdown. The nominal output voltage
is set by a 5-bit VID code. To accommodate the transition
time required by the newest processors for on-the-fly VID
changes, the ADP3203 features high-speed operation to
allow a minimized inductor size that results in the fastest
change of current to the output. To further allow for the
minimum number of output capacitors to be used, the
ADP3203 features active voltage positioning with ADOPTTM
optimal compensation to ensure a superior load transient
response. The output signal interfaces with the ADP3415
MOSFET driver that is optimized for high speed and high
efficiency for driving both the top and bottom MOSFETs of
the buck converter. The ADP3203 is capable of controlling
the synchronous rectifier to extend battery lifetime in light
load conditions.
SD 13
ENABLE _UVLO MAIN BIAS
PWRGD BLANKER
SR CONTROL
15
17
DRVLSD
COREFB
12
11
PWRGD
COREGD MONITOR
DPRSLP
DSLP
16
14
SS-HICCUP TIMER & OCP
SS
VID MUX &
SHIFT
10
9
SELECTOR
CLAMP
BOM
OVP & RVP
PM MODULE
19
GND
REV. PrD 1/02
Information furnished by Analog Devices is believed to be accurate and
reliable. However, no responsibility is assumed by Analog Devices for its
use, nor for any infringements of patents or other rights of third parties
which may result from its use. No license is granted by implication or
otherwise under any patent or patent rights of Analog Devices.
One Technology Way, P.O. Box 9106, Norwood. MA 02062-9106, U.S.A.
Tel:781/329-4700
Fax:781/326-8703
www.analog.com
©ANALOG DEVICES, INC., 2002
PRELIMINARY TECHNICAL DATA
( TA = 25 °C, High (H) = VCC, Low (L) = 0 V, VCC = 3.3 V, SD = H, VCOREFB
VDAC (≡ VDACOUT), VREG = VCS– = VVID = 1.25 V, ROUT = 100 kΩ, COUT = 10 pF,
CSS = 47 nF, RPWRGD = 680 Ω to 1.2 V, RCLAMP = 5.1 kΩ to VCC, HYSSET, BSHIFT,
=
ADP3203–SPECIFICATIONS1
DSHIFT are open, BOM = H, DSLP = H, DPRSLP = L, unless otherwise noted) Current sunk by a pin has a positive sign, sourced by a pin has a
negative sign. Negative sign is disregarded for min and max values.
Parameter
Symbol
Conditions
Min
Typ
Max
Units
SUPPLY-UVLO-SHUTDOWN
Normal Supply Current
UVLO Supply Current
ICC
ICCUVLO
ICCSD
7
15
425
mA
µA
µA
Shutdown Supply Current
SD = L, 3.0 V ≤ VCC ≤ 3.6 V
10
UVLO Threshold
SD = H
VCC ramping up, VSS= 0 V
VCC ramping down,
VCCH
VCCL
2.9
V
V
2.65
50
VSS floating
UVLO Hysteresis
VCCHYS
VSDTH
mV
V
Shutdown Threshold (CMOS Input)
VCC/2
POWERGOOD-CORE FEEDBACK
Core Feedback Threshold Voltage
VCOREFBH
0.9 V < VDAC < 1.675 V
VCOREFB ramping up
1.12 VDAC
1.10 VDAC
0.88 VDAC
0.86 VDAC
1.14 VDAC
1.12 VDAC
0.90 VDAC
0.88 VDAC
V
V
V
V
V
V
COREFB ramping down
COREFB ramping up
VCOREFB ramping down
Power Good Output Voltage
(open drain output)
VPWRGD
VCOREFB = VDACOUT
VCOREFB = 0.8 VDACOUT
0.95 VCC
0
VCC
0.8
V
V
Masking Time2
tPWRGD,MSK
VCC
=
3.3 V
100
µs
6
SOFT-START/HICCUP TIMER
Charge/Discharge Current
ISS
VSS = 0 V
VSS = 0.5 V
–
0.5
16
µA
µA
Soft-Start Enable/Hiccup
Termination Threshold
VREG = 1.25 V,
VRAMP = VCOREFB = 1.27 V
VSS ramping down
VSS ramping up
VSSENDWN
VSSENUP
80
150
200
mV
mV
7
Soft-Start Termination/Hiccup
Enable Threshold
VSSTERM
VRAMP = VCOREFB = 1.27 V
VSS ramping up
1.75
2.00
2.25
V
VID DAC
VID Input Threshold (CMOS Inputs)
VID Input Current
(Internal Active Pull-up)
Output Voltage
VVID0..4
IVID0..4
VCC/2
90
V
µA
VID 0..4 = L
VDAC
See VID Code Table 1
0.600
–1.0
–8.5
1.750
+1.0
+8.5
V
%
mV
µs
Accuracy
∆VDAC/VDAC 0.850 V < VDAC < 1.750 V
0.600 V < VDAC < 0.825 V
∆VDAC = 0.5 V, CDAC = 10 nF
Settling Time2
tDACS
3.5
3
Notes:
1 All limits at temperature extremes are guaranteed via correlation using standard Statistical Quality Control (SQC) methods.
2
Guaranteed by characterization.
Measured from 50% of VID code transition amplitude to the point where VDACOUT settles within 1% of its steady state value.
40 mVPP amplitude impulse with 20 mV overdrive. Measured from the input threshold intercept point to 50% of the output voltage swing.
Measured between the 30% and 70% points of the output voltage swing.
3
4
5
6 Two test conditions: 1)PWRGD is OK but forced to fail by applying an out-of-the-CoreGood-window voltage (VCOREFB,BAD = 1.0 V at VVID = 1.25 V setting) to
the COREFB pin right after the moment that BOM or DPRSLP is asserted/de-asserted. PWRGD should not fail immediately only with the specified blanking
delay time. 2) PWRGD is forced to fail (VCOREFB,BAD = 1.0 V at VVID = 1.25 V setting) but gets into the CoreGood-window
(VCOREFB,GOOD = 1.25 V) right after the moment that BOM or DPRSLP is asserted/de-asserted. PWRGD should not go high immediately only with the specified
blanking delay time.
7Guaranteed by design.
–2–
REV. PrD
PRELIMINARY TECHNICAL DATA
ADP3203
Parameter
Symbol
Conditions
Min
Typ
Max
Unit
CORE COMPARATOR
Input Offset Voltage (Ramp-Reg)
Input Bias Current
VCOREOS
IREG, IRAMP
VOUT_H
VREG = 1.25 V
VREG = VRAMP = 1.25 V
VCC = 3.0 V
VCC = 3.6 V
TA = 25°C
1.5
1
mV
µA
V
Output Voltage (OUT1,OUT2)
2.5
0
3.0
0.8
30
40
10
10
VOUT_L
tRMPOUT_PD
V
Propagation Delay Time2
Rise and Fall Time2
ns
ns
ns
ns
ns
ns
4
TA = Full Range
5
tOUT_R
tOUT_F
7
7
5
Noise Blanking Time2
tBLNK
OUT L-H Transition
OUT H-L Transition
80
120
CURRENT LIMIT
COMPARATOR
Input Offset Voltage
VCLIMOS
VCS- = 1.25 V
4
6
mV
Input Bias Current
Propagation Delay Time2
I
CS+, ICS-
VCS+ = 1.25 V
TA = 25° C
TA = Full Range
–5
30
50
–
60
100
3
µA
ns
ns
4
tCLPD
CURRENT SENSE MULTIPLEXER
Trans-Resistance
RCS1-CS+
RCS2-CS+
VCS1 = VCS2
,
Switch is ON
Switch is OFF
150
100
Ω
MΩ
V
Common Mode Voltage Range7
0
2
HYSTERESIS SETTING
Hysteresis Current
IRAMP_H
,
VREG = 1.25 V
-ICSP_H
VRAMP = 1.23 V,BOM=H
I
HYSSET = 10 µA
–8
–80
–10
–100
–12
–120
µA
µA
IHYSSET = 100 µA
V
V
V
RAMP = 1.27 V, BOM = H
I
HYSSET = 10 µΑ
8
80
10
100
12
120
µΑ
µΑ
IHYSSET = 100 µΑ
RAMP = 1.23 V, BOM = L
I
HYSSET = 10 µΑ
–6.4
–64
–8
–80
–9.6
–96
µΑ
µΑ
IHYSSET = 100 µΑ
RAMP = 1.27 V, BOM = L
I
HYSSET = 10 µΑ
64
64
8
80
96
96
µΑ
µA
IHYSSET = 100 µΑ
Hysteresis Reference Voltage
VHYSSET
1.53
1.7
1.87
V
CURRENT LIMIT SETTING
Hysteresis Current
ICS–
VRAMP = 1.23 V
VREG = VCS– COREFB = 1.25 V
CS+ = 1.23 V BOM = H
=
V
V
IHYSSET = 10 µΑ
IHYSSET = 100 µΑ
–27
–31.5
–36
µA
µA
–268
–301.5 –335
VCS+ = 1.27 V, BOM = H
IHYSSET = 10 µΑ
–18
–21.5
–25
µA
µA
IHYSSET = 100 µΑ
–178
–201.5 –225
VCS+ = 1.23 V, BOM = L
IHYSSET = 10 µΑ
–21
–25.5
–30
µA
µA
IHYSSET = 100 µΑ
CS+ = 1.27 V, BOM = L
IHYSSET = 10 µΑ
–212
–241.5 –271
V
–14
–17.5
–21
µA
µA
IHYSSET = 100 µΑ
–140
–161.5 –183
REV. PrD
–3–
PRELIMINARY TECHNICAL DATA
ADP3203–SPECIFICATIONS1
Parameter
Symbol
Conditions
Min
Typ
Max
Units
SHIFT SETTING
Battery-Shift Current
IRAMPB,ICS+B
VVID = 1.25 V
RBSHIFT = 12.5 k, BOM = L
DSLP = H
–90
–100
–110
µA
Battery-Shift Reference Voltage
DeepSleep-Shift Current
VBSHIFT
VDAC
–100
V
IRAMPD,ICS+D
VVID = 1.25 V
–90
–110
µA
RDSHIFT = 12.5 k, BOM = H
DSLP = L
DeepSleep-Shift Reference Voltage
VDSHIFT
VDAC
V
SHIFT CONTROL INPUTS
BOM Threshold
(CMOS Input)
DSLP Threshold
(VTT-Level CMOS Input)
DPRSLP Mode Threshold
(CMOS Input)
VBOM
VCC/2
0.9
V
V
V
VDSLP
VDPRSLP
VCC/2
LOW-SIDE DRIVE CONTROL
Output Voltage (CMOS Output)
VDRVLSD
IDRVLSD
DPRSLP = H
DPRSLP = L
VDRVLSD = 1.5 V
DPRSLP = L
DPRSLP = H
0
0.4
VCC
V
V
0.7 VCC
Output Current
0.5
–0.5
mA
mA
OVER/REVERSE VOLTAGE
PROTECTION-CORE FEEDBACK
Over-Voltage Threshold
VCOREFB,OVP
VCOREFB rising
VCOREFB falling
2.0
1.95
V
V
Reverse-Voltage Threshold
VCOREFB,OVP
VCOREFB falling
VCOREFB rising
–0.3
–0.1
V
V
V
Output Voltage (Open Drain Output)
Output Current
VCLAMP
ICLAMP
0.7 VCC
VCC
10
VCLAMP = 1.5 V, VVID = 1.25 V
VCOREFB = VDAC
µA
VCOREFB = 2.2 V
1
4
mA
ORDERING GUIDE
DPRSLP
Voltage
Temperature
Range
Package
Option
Model
ADP3203JRU-0.85-RL
ADP3203JRU-1.0-RL
ADP3203JRU-1.0-RL7
0.85 V
1 V
1 V
0°C to 100°C
0°C to 100°C
0°C to 100°C
TSSOP-28
TSSOP-28
TSSOP-28
ABSOLUTE MAXIMUM RATINGS*
Input Supply Voltage (VCC) ............................. -0.3 V to +7 V
UVLO Input Voltage ......................................... -0.3 V to +7 V
All Other Inputs/Outputs..................................... VCC + 0.3 V
Operating Ambient Temperature Range ........... 0°C to +100°C
Junction Temperature Range ............................ 0°C to +150°C
θJA ............................................................................... 98°C/W
Storage Temperature Range ............................ -65°C to 150°C
Lead Temperature (Soldering, 10 sec.) ........................ +300°C
*This is a stress rating only; operation beyond these limits can cause the device
to be permanently damaged.
–4–
REV. PrD
PRELIMINARY TECHNICAL DATction Description
ADP3203
PIN FUNCTION DESCRIPTIONS
Function
Pin
Mnemonic
1
HYSSET
Hysteresis Set. This is an analog I/O pin whose output is a fixed voltage reference and whose input
is a current that is programmed by an external resistance to ground. The current is used in the IC
to set the hysteretic currents for the Core Comparator and the Current Limit Comparator.
Modification of the resistance will affect both the hysteresis of the feedback regulation and the
current limit set point and hysteresis.
2
3
DSHIFT
BSHIFT
Deep Sleep Shift. This is an analog I/O pin whose output is the VID reference voltage and whose
input is a current that is programmed by an external resistance to ground. The current is used in
the IC to set a switched bias current out of the RAMP pin, depending on whether it is activated by
the DSLP# signal. When activated, this added bias current creates a downward shift of the
regulated core voltage to a predetermined optimum level for regulation corresponding to Deep
Sleep mode of CPU operation. The use of the VID code as the reference makes the Deep Sleep
offset a fixed percentage of the VID setting, as required by specifications.
Battery Optimized Mode (BOM) Shift. This is an analog I/O pin whose output that is the VID
reference voltage and whose input current is programmed by an external resistance to ground. The
current is used in the IC to set a switched bias current out of the RAMP pin, depending on
whether it is activated by the BOM signal. When activated, this added bias current creates a
downward shift of the regulated core voltage to a predetermined optimum level for regulation
corresponding to Battery Optimized Mode of CPU operation. The use of the VID code as the
reference makes the DSHIFT a fixed percentage of the VID setting, as required by specifications.
4–8
VID[4:0]
Voltage Identification Inputs. These are the VID inputs for logic control of the programmed
reference voltage that appears at the DACOUT pin, and, via external component configuration, is
used for setting the output voltage regulation point. The VID pins have a specified internal pullup
current such that, if left open, the pins will default to a logic high state. The VID code does not set
the DAC output voltage directly but through a transparent latch which is clocked by the BOM
pin's GMUXSEL signal rising and falling edge.
9
BOMꢀ
Battery Optimized Mode Control (active low). This is a digital input pin that corresponds to the
system's GMUXSEL signal that corresponds to Battery Optimized Mode of the CPU operation in
its active low state and Performance Optimized Mode (POM) in its deactivated high state. The
signal also controls the optimal positioning of the core voltage regulation level by offsetting it
downwards in Battery Optimized Mode according to the functionality of the BSHIFT and RAMP
pins. It is also used to initiate a masking period for the PWRGD signal whenever a GMUXSEL
signal transition occurs.
10
11
DSLPꢀ
Deep Sleep Mode Control (active low). This is a digital input pin corresponding to the system's
STPꢀCPU signal which, in its active state, corresponds to Deep Sleep mode of the CPU operation,
which is a subset operating mode of either BOM or POM operation. The signal controls the
optimal positioning of the core voltage regulation level by offsetting it downwards according to the
functionality of the DSHIFT and RAMP pins.
DPRSLP
Deeper Sleep Mode Control (active high). This is a digital input pin corresponding to the system's
DPRSLPVR signal corresponding to Deeper Sleep mode of the CPU operation. The signal when
it is activated controls the DAC output voltage by disconnecting the VID signals from the DAC
input and setting a specified internal Deeper Sleep code instead. At de-assertion of the
DPRSLPVR signal, the DAC output voltage returns to the voltage level determined by the
external VID code. The DPRSLPVR signal is also used to initiate a blanking period for the
PWRGD signal to disable its response to a pending dynamic core voltage change corresponds to
the VID code transition.
REV. PrD
–5–
PRELIMINARY TECHNICAL DATA
ADP3203
Pin
Mnemonic
Function
12
PWRGD
Power Good (active high). This is an open drain output pin which, via the assistance of an
external pull-up resistor to the desired voltage, indicates that the core voltage is within the
specified tolerance of the VID programmed value or else in a VID transition state as indicated
by a recent state transition of either the BOM or DPRSLP pins. PWRGD is deactivated
(pulled low) when the IC is disabled or in UVLO mode or starting up, or the COREFB
voltage is out of the core powergood window. The open drain output allows external wired
ANDing (logical NORing) with other open drain/collector power-good indicators.
13
14
SD
Shutdown (active low). This is a digital input pin coming from a system signal which, in its
active state, shuts down the IC operation, placing the IC in its lowest quiescent current state
for maximum power savings.
CLAMP
Clamp (active high). This is an open drain output pin which, via the assistance of an external
pull-up resistor, indicates that the core voltage should be clamped for its protection. To allow
the highest level of protection, the CLAMP signal is developed using both a redundant
reference and a redundant feedback path with respect to those of the main regulation loop.
The signal is timed out using the softstart capacitor, so an external current protection
mechanism (e.g., fuse or AC adapter's current limit) should be tripped within ~3 times the
programmed soft start time (e.g. 5~10 ms). In a preferred and more conservative configura-
tion, the core voltage is clamped by an external FET. The initial protection function is served
when it is activated by detection of either an over-voltage or a reverse-voltage condition on the
COREFB pin. A backup protection function due to loss of the latched signal at IC power-off
is served by connecting the pull-up resistor to a system "ALWAYS" regulator output (e.g.,
V5_ALWAYS). If the external FET is used, this implementation will keep the core voltage
clamped until the ADP3422 has power re-applied, thus keeping protection for the CPU even
after a hard-failure power-down and restart (e.g., a shorted top or bottom FET).
15
16
DRVLSD
Drive-Low Shutdown (active low). This is a digital output pin which, in its active state,
indicates that the lower FET of the core VR should be disabled. In the suggested application
schematic this pin is directly connected to the pin of the same name on the ADP3415 or other
driver IC. Drive-low shutdown is normally activated by the DPRSLP signal, corresponding to
a light load condition, but a number of dynamic conditions can override the control of this pin
as needed.
SS
Soft Start. This is an analog I/O pin whose output is a controlled current source used to
charge or discharge an external grounded capacitor and whose input is the detected voltage
that is indicative of elapsed time. The pin controls the soft start time of the IC as well as the
hiccup cycle time during overload including but not limited to short circuit, over voltage, and
reverse voltage. Hiccup operation is a feature that was added to reduce short circuit power
dissipation by more than an order of magnitude, while still allowing an automatic restart when
the failure mode ceased. The hiccup operation can be overwritten and changed to latched-off
operation by clamping the SS pin voltage to a voltage level somewhere above ~ 0.2 V. In this
configuration, the controller does not restart after a hiccup cycle is initiated, but stays latched
off.
17
18
COREFB
DACOUT
Core Feedback. This is a high-impedance analog input pin that is used to monitor the output
voltage for setting the proper state of the PWRGD and CLAMP pins. It is generally recom-
mended to RC-filter the ripple and noise from the monitored core voltage, as suggested by the
application schematic.
Digital-to-Analog Converter Output. This output voltage is the VID-controlled reference
voltage whose primary function is to determine the output voltage regulation point.
19
20
GND
Ground.
OUT1
Output to Driver 1. This is a digital output pin which is used to command the state of the
switched node via the driver and MOSFET switches. It should be connected to the IN pin of
the ADP3415 driver that corresponds to the first of two channels.
–6–
REV. PrD
PRELIMINARY TECHNICAL DATA
ADP3203
Pin
Mnemonic
Function
21
OUT2
Output to Driver 2. This is a digital output pin which is used to command the state of the
switched node via the driver. It should be connected to the IN pin of the ADP3415 driver that
corresponds to the second of two channels.
22
23
CS1
CS2
Current Sense, Channel 1. This is a high-impedance analog input pin which is used for providing
negative feedback of the current information for the first of two channels.
Current Sense, Channel 2. This is a high-impedance analog input pin which is used for providing
negative feedback of the current information for the second of two channels. The pin is also used
to determine whether the chip is acting as a single or dual-phase controller. If the pin is tied to
VCC but not a sense resistor then the dual-phase operation is disabled; the chip works as a single
phase controller. In this condition the second phase's output signal (OUT2) is not switching but
stays static low.
24
25
VCC
Power supply. This should be connected to the system's 3.3 V power supply output.
RAMP
Regulation Ramp Feedback Input. The RAMP pin voltage is compared against the REG pin for
cycle-by-cycle switching response. Several switched current sources also appear at this input, the
cycle-by-cycle hysteresis-setting switched current programmed by the HYSSET pin, the BOM
shift current programmed by the BSHIFT pin, and the Deep Sleep shift current programmed by
the DSHIFT pin. The external resistive termination at this pin sets the magnitude of the hysteresis
applied to the regulation loop.
26
27
REG
CS+
Regulation Voltage Summing Input. This is a high-impedance analog input pin into which the
voltage reference of the feedback loop allows the summing of both the DACOUT voltage and the
core voltage for programming the output resistance of the core voltage regulator. This is also the
pin at which an optimized transient response can be tailored using Analog Devices' patented
ADOPT design technique.
Current Limit Positive Sense. This is a high-impedance analog input pin that is multiplexed
between either of the two current-sense inputs during the high state of the OUT pin of the
respective channel. During the common off-time of both channels the pin's voltage reflects the
average of the two channels. The multiplexed current sense signal is passed to the core comparator
through an external resistive termination connected from this pin to the RAMP pin. The external
(RAMP) resistor sets the magnitude of the hysteresis applied to the regulation loop.
28
CS-
Current Limit Negative Sense. This is a high-impedance analog input pin which is normally
Kelvin connected via a current-limit programming resistor to the negative node of the current
sense resistor(s). A hysteretically-controlled current - three times the current programmed at the
HYSSET pin - also flows out of this pin and develops a current-limit-setting voltage across that
resistor which then must be matched by the inductor current flowing in the current sensing
resistor in order to trigger the current limit function. When triggered, the current flowing out of
this pin is reduced to two-thirds of its previous value, producing hysteresis in the current limiting
function.
REV. PrD
–7–
PRELIMINARY TECHNICAL DATA
ADP3203
M B R S 1 3 0 L T 3
D 6
M B R S 1 3 0 L T 3
D 5
Figure 1. Typical Application
–8–
REV. PrD
PRELIMINARY TECHNICAL DATA
ADP3203
THEORY OF OPERATION
Overview
along the load line (which is synonymous with an output
resistance of the power converter). The core voltage is also
offset by a DC value – usually specified as a percentage –
depending on the operating mode. The voltage offset is also
called a “shift”.
Featuring a new proprietary single-or-dual-channel buck
converter hysteretic control architecture developed by Analog
Devices, Inc., the ADP3203 is the optimal core voltage control
solution for both IMVP-II & -III generation microprocessors.
The complex multi-tiered regulation requirements of either
IMVP specification are easily implemented with the highly
integrated functionality of this controller.
Two pins, BSHIFT and DSHIFT, are used to program the
magnitude of the voltage shifts. The voltage shifts are accom-
plished by injecting current at the node of the negative input
pin of the feedback comparator. Resistive termination at the
pins determines the magnitude of the voltage shifts.
Power Conversion Control Architecture
Driving of the individual channels is accomplished using
external drivers, such as the ADP3415. One PWM interface pin
per channel, OUT1 and OUT2, is provided. A separate pin,
DRVLSD, commands the driver to enable or disable synchro-
nous operation during the off time of each channel. The same
DRVLSD pin is connected to both drivers.
Two other pins, BOM and DSLP, are used to activate the
respective two shifts only in their active low states. In the
ADP3203, the shifts are mutually exclusive, with the
DeepSleep shift (controlled by DSLP and DSHIFT pins) being
the dominant one. Another pin, DPRSLP, eliminates both
shifts only in its active high state. Its assertion corresponds to
the DeeperSleep operating mode.
The ADP3203 utilizes hysteretic control. The resistor from the
HYSSET pin to ground sets up a current that is switched bi-
directionally into a resistor interconnected between RAMP and
CS+ pins. The switching of this current sets the hysteresis.
Current Limiting
The current programmed at the HYSSET pin and a resistor
from the CS- pin to the common node of the current sense
resistors sets the current limit. If the current limit threshold is
triggered, a hysteresis is applied to the threshold so that
hysteretic control is maintained during a current limited
operating mode.
In its dual-channel configuration, the hysteretic control requires
multiplexing information in the two channels. The inductor
current of the channel that is driven high is controlled against
the upper hysteresis limit. During the common off-time of the
two channels, the inductor currents are averaged together and
compared against the lower hysteresis limit. This proprietary
off-time averaging technique serves to eliminate a systematic
offset that otherwise appears in a fully multiplexed hysteretic
control system.
Softstart and Hiccup
A capacitor from the SS pin to determines both the soft-start
time and the frequency at which hiccup will occur under a
continuous short circuit or overload.
System Signal Interface
Compensation
Several pins of the ADP3203 are meant to connect directly to
system signals. The VID pins connect to the system VID
control signals. The DPRSLP pin connects to the system’s
DPRSLPVR signal. The DSLP pin connects to the system’s
DPSLP or STPCPU signal. The BOM signal connects to the
system’s GMUXSEL signal. In an IMVP-II system, the
GMUXSEL signal preceeds any VID code change with a few
nanoseconds, while in an IMVP-III system, it follows it with a
maximum 12 µs delay. To comply with both specifications, the
ADP3203 has a VID register in front of the DAC inputs that is
written by a short pulse generated at the rising or falling edge of
the GMUSEL signal. In an IMVP-II configuration, if the
external VID multiplex settling time is longer than the internal
VID register's write pulse-width, then the insertion of an
external RC delay network in the GMUXSEL signal path (in
front of the BOM pin) is recommended. The Intel spec calls for
maximum 200 ns VID code set-up time. This specification can
be met with a simple RC network which consists of only a
220 kΩ resistor, and no external capacitor just the BOM pin's
capacitance.
As with all ADI products for core voltage control, the controller
is compatible with ADOPT™ compensation, which provides
the optimum output voltage containment within a specified
voltage window or along a specified load-line using the fewest
possible number of output capacitors. The inductor ripple
current is kept at a fixed programmable value while the output
voltage is regulated with fully programmable voltage positioning
parameters, which can be tuned to optimize the design for any
particular CPU regulation specifications. By controlling the
ripple current rather than ripple voltage, the frequency varia-
tions associated with changes in output impedance for standard
ripple regulators will not appear.
Feedback/Current Sensing
Accurate current sensing is needed to accomplish output
voltage positioning accurately, which, in turn, is required to
allow the minimum number of output capacitors to be used to
contain transients. A current sense resistor is used between
each inductor and the output capacitors. To allow the control
to operate without amplifiers, the negative feedback signal is
multiplexed from the inductor, or upstream, side of the current
sense resistors, and a positive feedback signal, if needed for
load-line tuning is taken from the output, or downstream, side.
Undervoltage Lockout
The ADP3203’s supply pin, VCC, has undervoltage lockout
(UVLO) functionality to ensure that if VCC is too low to
maintain proper operation, the IC will remain off and in a low
current state.
Output Voltage Programming by VID, Offsets, & Load-Line
In the IMVP-II & -III specifications, the output voltage is a
function of both the core current – according to a specified load
line – and the system operating mode – i.e., performance or
battery optimized, normal or deepsleep clocking state, or
deepersleep. The VID code programs the “nominal” core
voltage. The core voltage decreases as a function of load current
REV. PrD
–9–
PRELIMINARY TECHNICAL DATA
ADP3203
Over-Voltage Protection (OVP) & Reverse-Voltage
Protection (RVP)
The ADP3203 maximizes the integration of IMVP-3
features. Therefore, no additional externally implemented
functions are required to comply with IMVP-3 specifica-
tions. This saves PCB area for component placement on the
motherboard.
The ADP3203 features a comprehensive redundantly moni-
tored OVP and RVP implementation to protect the CPU core
against an excessive or reverse voltage, e.g., as might be
induced by a component or connection failure in the control or
power stage. Two pins are associated with the OVP/RVP
circuitry – a pin for output voltage feedback, COREFB, which
is used also for power good monitoring but not for voltage
regulation, and an output pin, CLAMP.
PCB Layout Consideration for ADP3203/3415
The following guidelines are recommended for optimal
performance of the ADP3203 and ADP3415 in a power
converter. The circuitry is considered in three parts: the power
switching circuitry, the output filter, and the control circuitry.
The CLAMP pin defaults to a low state at startup of the
ADP3203 and remains low until an OV or RV condition is
detected. If either condition is detected, the CLAMP pin is
switched and latched to the VCC pin. The high state of the
CLAMP pin is reset only after several milliseconds as the
softstart pin discharges.
Placement Overview
1. For ideal component placement, the output filter
capacitors will divide the power switching circuitry from
the control section. As an approximate guideline,
considered on a single-sided PCB, the best layout would
have components aligned in the following order:
ADP3415, MOSFETs and input capacitor, output
inductor, current sense resistor, output capacitors,
control components and ADP3203. Note that the
ADP3203 and ADP3415 are completely separated for
an ideal layout, which is impossible with a single-chip
solution. This keeps the noisy switched power section
isolated from the precision control section and gives
more freedom in the layout of the power switching
circuitry.
For maximum and fastest protection, the CLAMP pin
should be used to drive the gate of a power MOSFET
whose drain-source is connected across the CPU core
voltage. Detection of OV or RV will clamp the core voltage
to essentially zero, thus quickly removing the fault condition
and preventing further energy from being applied to the
CPU core.
For a less comprehensively protective but also less costly
solution, the CLAMP pin may be used to latch the discon-
nection of input power. The latch should be powered
whenever any input power source is present. Typically,
such a latching circuit is already present in a system design,
so it becomes only a matter of allowing the CLAMP pin to
also trigger the latch. In this configuration, the latched off
state of the system would be indicative of a system failure.
The OV/RV protective means is via not allowing the
continued application of energy to the CPU core. The
design objective should be to ensure that the CPU core
could safely absorb the remaining energy in the power
converter, however, since this energy is not clamped as in
the preferred configuration.
2. Whenever a power-dissipating component (e.g., a power
MOSFET) is soldered to a PCB, the liberal use of vias,
both directly on the mounting pad if possible and
immediately surrounding it, is recommended. Two
important reasons for this are: improvement of the
current rating through the vias (if it is a current path),
and improved thermal performance- especially if there is
opportunity to spread the heat with a plane on the
opposite side of the PCB.
Power Switching Circuitry
ADP3415, MOSFETs, and Input Capacitors
3. Locate the ADP3415 near the MOSFETs so the loop
inductance in the path of the top gate drive returned to the
SW pin is small, and similarly for the bottom gate drive
whose return path is the ground plane. The GND pin
should have at least one very close via into the ground
plane.
LAYOUT CONSIDERATIONS
Advantages in PCB Layout
Analog Devices Inc., provides ADP3203/3415 as a dedicated
2-phase power management solution for IMVP-3 Intel P4
mobile core supply.
This 2-phase solution separates the controller (ADP3203)
and MOSFET driver (ADP3415). Today, most
motherboards only leave small pieces of PCB area for power
management circuit. Therefore, the separation of the
controller and the MOSFET drivers gives much greater
freedom in layout than any single chip solution can do.
4. Locate the input bypass MLC capacitors close to the
MOSFETs so that the physical area of the loop enclosed
in the electrical path through the bypass capacitor and
around through the top and bottom MOSFETs (drain-
source) is small and wide. This is the switching power
path loop.
Meanwhile, the separation also provides the freedom to
place the analog controller in a relatively quiet area in the
motherboard. This can minimize the susceptibility of the
controller to injected noise. Any single chip solution with a
high speed loop design will suffer larger susceptibility to
jitter that appears as modulation of the output voltage.
5. Make provisions for thermal management of all the
MOSFETs. Heavy copper and wide traces to ground
and power planes will help to pull the heat out.
Heatsinking by a metal tap soldered in the power plane
–10–
REV. PrD
PRELIMINARY TECHNICAL DATA
ADP3203
near the MOSFETs will help. Even just small airflow
can help tremendously. Paralleled MOSFETs to achieve
a given resistance will help spread the heat.
15. Absolutely avoid crossing any signal lines over the
switching power path loop, described previously.
16. Accurate voltage positioning depends on accurate
current sensing, so the control signals which monitor the
voltage differentially across the current sense resistor
should be kelvin connected. Please refer to ADI Evalua-
tion Board of the ADP3203 and its documentation for
control signal connection with sense resistors.
6. An external "antiparallel" schottky diode (across the
bottom MOSFET) may help efficiency a small amount
(< ~1 %) depending on its forward voltage drop com-
pared to the MOSFET's body diode at a given current; a
MOSFET with a built in antiparallel schottky is more
effective. For an external schottky, it should be placed
next to the bottom MOSFET or it may not be effective
at all.
17. The RC filter used for the current sense signal should be
located near the control components as this serves the
dual purpose of filtering out the effect of the current
sense resistors' parasitic inductance and noise picked up
along the routing of the signal. The former purpose is
achieved by having the time constant of the RC filters
approximately matched to that of the sense resistors and
is important for maintaining the accuracy of the current
signal.
7. The VCC bypass capacitor should be close to the VCC
pin and connected on either a very short trace to the
GND pin or to the GND plane.
Output Filter
Output Inductor and Capacitors, Current Sense Resistor
8. Locate the current sense resistors very near to the output
voltage plane.
TABLE 1. VID CODE
9. The load-side heads of two sense resistors should join as
closely as possible for accurate current signal measure-
ment of each phase.
VID4
VID3
VID2
VID1
VID0
VOUT
0
0
0
0
0
0
0
0
0
0
0
0
0
0
0
0
1
1
1
1
1
1
1
1
1
1
1
1
1
1
1
1
0
0
0
0
0
0
0
0
1
1
1
1
1
1
1
1
0
0
0
0
0
0
0
0
1
1
1
1
1
1
1
1
0
0
0
0
1
1
1
1
0
0
0
0
1
1
1
1
0
0
0
0
1
1
1
1
0
0
0
0
1
1
1
1
0
0
1
1
0
0
1
1
0
0
1
1
0
0
1
1
0
0
1
1
0
0
1
1
0
0
1
1
0
0
1
1
0
1
0
1
0
1
0
1
0
1
0
1
0
1
0
1
0
1
0
1
0
1
0
1
0
1
0
1
0
1
0
1
1.750
1.700
1.650
1.600
1.550
1.500
1.450
1.400
1.350
1.300
1.250
1.200
1.150
1.100
1.050
1.00
0.975
0.950
0.925
0.900
0.875
0.850
0.825
0.800
0.775
0.750
0.725
0.700
0.675
0.650
0.625
0.600
10. PCB trace resistances from the current sense resistors to
the regulation point should be minimized, known
(calculated or measured), and compensated for as part
of the design if it is significant. (Remote sensing is not
sufficient for relieving this requirement!) A square
section of 1-ounce copper trace has a resistance of
~500 mΩ and this adds to the specified DC output
resistance of the power converter. The output capaci-
tors should similarly be close to the regulation point and
well tied into power planes as impedance here will add
to the "AC output resistance" (i.e., the ESR) that is
implicitly specified as well.
11. Whenever high currents must be routed between PCB
layers, vias should be used liberally to create parallel
current paths so that the resistance and inductance is
minimized and the via current rating is not exceeded.
Control Circuitry
ADP3203, Control Components
12. If the ADP3203 cannot be placed as previously recom-
mended, at the least care should be taken to keep the
device and surrounding components away from radia-
tion sources (e.g., from power inductors) and capacitive
coupling from noisy power nodes.
13. Noise immunity can be improved by the use of a
devoted signal ground plane for the power controller
and its surrounding components. Space for a ground
plane might readily be available on a signal plane of the
PCB since it is often unused in the vicinity of the power
controller.
14. If critical signal lines (i.e., signals from the current sense
resistor leading back to the ADP3203) must cross
through power circuitry, it is best if a signal ground
plane can be interposed between those signal lines and
the traces of the power circuitry. This serves as a shield
to minimize noise injection into the signals.
REV. PrD
–11–
PRELIMINARY TECHNICAL DATA
ADP3203
OUTLINE DIMENSIONS
Dimensions shown in inches and (mm).
28-Lead Thin Shrink Small Outline Package (TSSOP)
(RU-28)
0.386 (9.80)
0.378 (9.60)
28
15
0.177 (4.50)
0.169 (4.30)
0.256 (6.50)
0.246 (6.25)
1
14
PIN 1
0.006 (0.15)
0.002 (0.05)
0.0433 (1.10)
MAX
8؇
0؇
0.0256 (0.65) 0.0118 (0.30)
0.028 (0.70)
0.020 (0.50)
0.0079 (0.20)
0.0035 (0.090)
SEATING
PLANE
BSC
0.0075 (0.19)
–12–
REV. PrD
相关型号：
ADP3203JRUZ-1.0-RL7
IC SWITCHING CONTROLLER, PDSO28, TSSOP-28, Switching Regulator or Controller
ADI
©2020 ICPDF网 联系我们和版权申明