OP27 [ADI]
Low-Noise, Precision Operational Amplifier; 低噪声，高精度运算放大器
| 型号： | OP27 |
| 厂家： | 
ADI |
| 描述： | Low-Noise, Precision Operational Amplifier |
| 文件： | 总16页 (文件大小：366K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
Low-Noise, Precision
Operational Amplifier
a
OP27
PIN CONNECTIONS
FEATURES
Low Noise: 80 nV p-p (0.1 Hz to 10 Hz), 3 nV/
Low Drift: 0.2 ꢀV/ꢁC
High Speed: 2.8 V/ꢀs Slew Rate, 8 MHz Gain
Bandwidth
√Hz
TO-99
(J-Suffix)
BAL
Low VOS: 10 ꢀV
Excellent CMRR: 126 dB at VCM of 11 V
High Open-Loop Gain: 1.8 Million
Fits 725, OP07, 5534A Sockets
Available in Die Form
V+
BAL 1
OP27
OUT
–IN 2
NC
+IN 3
GENERAL DESCRIPTION
4V– (CASE)
NC = NO CONNECT
The OP27 precision operational amplifier combines the low
offset and drift of the OP07 with both high speed and low noise.
Offsets down to 25 µV and drift of 0.6 µV/°C maximum make
the OP27 ideal for precision instrumentation applications.
Exceptionally low noise, en = 3.5 nV/√Hz, at 10 Hz, a low 1/f
noise corner frequency of 2.7 Hz, and high gain (1.8 million),
allow accurate high-gain amplification of low-level signals. A
gain-bandwidth product of 8 MHz and a 2.8 V/µsec slew rate
provides excellent dynamic accuracy in high-speed, data-
acquisition systems.
8-Pin Hermetic DIP
(Z-Suffix)
Epoxy Mini-DIP
(P-Suffix)
8-Pin SO
(S-Suffix)
A low input bias current of 10 nA is achieved by use of a
bias-current-cancellation circuit. Over the military temperature
range, this circuit typically holds IB and IOS to 20 nA and 15 nA,
respectively.
1
2
3
4
8
7
6
5
V
TRIM
V
TRIM
–IN
+IN
V–
OS
OS
OP27
V+
OUT
NC
The output stage has good load driving capability. A guaranteed
swing of 10 V into 600 Ω and low output distortion make the
NC = NO CONNECT
OP27 an excellent choice for professional audio applications.
(Continued on page 7)
V+
C2
R3
R4
1
8
Q6
Q22
Q46
C1
V
ADJ.
OS
R23 R24
Q24
R1*
R2*
Q21
Q23
R9
Q20 Q19
OUTPUT
R12
Q1A Q1B
Q2B Q2A
NONINVERTING
INPUT (+)
C3
C4
R5
Q3
Q26
INVERTING
INPUT (–)
Q45
Q11 Q12
Q27
Q28
*R1 AND R2 ARE PERMANENTLY
ADJUSTED ATWAFERTEST FOR
MINIMUM OFFSETVOLTAGE.
V–
Figure 1. Simplified Schematic
REV. A
Information furnished by Analog Devices is believed to be accurate and
reliable. However, no responsibility is assumed by Analog Devices for its
use, norforanyinfringementsofpatentsorotherrightsofthirdpartiesthat
may result from its use. No license is granted by implication or otherwise
under any patent or patent rights of Analog Devices.
One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A.
Tel: 781/329-4700
Fax: 781/326-8703
www.analog.com
© Analog Devices, Inc., 2002
OP27–SPECIFICATIONS
(@ V = 15 V, T = 25ꢁC, unless otherwise noted.)
ELECTRICAL CHARACTERISTICS
S
A
OP27A/E
OP27F
OP27C/G
Parameter
Symbol Conditions
Min Typ Max Min Typ Max Min Typ Max Unit
INPUT OFFSET
VOLTAGE1
VOS
10
0.2
7
25
1.0
35
20
0.3
9
60
1.5
50
30
0.4
12
100
2.0
75
µV
LONG-TERM VOS
STABILITY2, 3
VOS/Time
µV/MO
nA
INPUT OFFSET
CURRENT
IOS
IB
INPUT BIAS
CURRENT
10
40
12
55
15
80
nA
INPUT NOISE
VOLTAGE3, 4
en p-p
en
0.1 Hz to 10 Hz
0.08 0.18
0.08 0.18
0.09 0.25 µV p-p
INPUT NOISE
Voltage Density3
fO = 10 Hz
fO = 30 Hz
fO = 1000 Hz
3.5
3.1
3.0
5.5
4.5
3.8
3.5
3.1
3.0
5.5
4.5
3.8
3.8
3.3
3.2
8.0
5.6
4.5
nV/√Hz
nV/√Hz
nV/√Hz
INPUT NOISE
in
fO = 10 Hz
fO = 30 Hz
fO = 1000 Hz
1.7
1.0
0.4
4.0
2.3
0.6
1.7
1.0
0.4
4.0
2.3
0.6
1.7
1.0
0.4
pA/√Hz
pA/√Hz
pA/√Hz
Current Density3, 5
0.6
INPUT
RESISTANCE
Differential-Mode6
Common-Mode
RIN
RINCM
1.3
6
3
0.94
5
2.5
0.7
4
2
MΩ
GΩ
INPUT VOLTAGE
RANGE
IVR
11.0 12.3
11.0 12.3
11.0 12.3
V
COMMON-MODE
REJECTION RATIO CMRR
VCM
=
11 V
114
126
1
106
123
1
100
120
2
dB
POWER SUPPLY
REJECTION RATIO
PSRR
VS = 4 V
to 18 V
10
10
20
µV/V
LARGE-SIGNAL
VOLTAGE GAIN
AVO
RL ≥ 2 kΩ,
VO = 10 V
RL ≥ 600 Ω,
VO = 10 V
1000 1800
1000 1800
700
600
1500
1500
V/mV
V/mV
800
1500
800
1500
OUTPUT
VOLTAGE SWING
VO
SR
RL ≥ 2 kΩ
12.0 13.8
10.0 11.5
12.0 13.8
10.0 11.5
11.5 13.5
10.0 11.5
V
V
RL ≥ 600 Ω
SLEW RATE7
RL ≥ 2 kΩ
1.7
2.8
1.7
2.8
1.7
2.8
V/µs
GAIN
BANDWIDTH
PRODUCT7
GBW
5.0
8.0
5.0
8.0
5.0
8.0
MHz
OPEN-LOOP
OUTPUT
RESISTANCE
RO
Pd
VO = 0, IO = 0
VO
70
90
70
90
70
Ω
POWER
CONSUMPTION
140
140
100
170
mW
OFFSET
ADJUSTMENT
RANGE
RP = 10 kΩ
4.0
4.0
4.0
mV
NOTES
1Input offset voltage measurements are performed ~ 0.5 seconds after application of power. A/E grades guaranteed fully warmed up.
2Long-term input offset voltage stability refers to the average trend line of VOS versus. Time over extended periods after the first 30 days of operation. Excluding the
initial hour of operation, changes in VOS during the first 30 days are typically 2.5 µV. Refer to typical performance curve.
3Sample tested.
4See test circuit and frequency response curve for 0.1 Hz to 10 Hz tester.
5See test circuit for current noise measurement.
6Guaranteed by input bias current.
7Guaranteed by design.
–2–
REV. A
OP27
ELECTRICAL CHARACTERISTICS
(@ VS = 15 V, –55ꢁC ≤ TA ≤ 125ꢁC, unless otherwise noted.)
OP27A
Typ
OP27C
Typ
Parameter
Symbol Conditions
Min
Max
Min
Max
Unit
INPUT OFFSET
VOLTAGE1
VOS
30
60
70
300
µV
AVERAGE INPUT
OFFSET DRIFT
2
TCVOS
3
TCVOSn
0.2
15
0.6
50
60
4
1.8
µV/°C
INPUT OFFSET
CURRENT
IOS
IB
30
35
135
nA
INPUT BIAS
CURRENT
20
150 nA
INPUT VOLTAGE
RANGE
IVR
10.3
108
11.5
122
2
10.2
11.5
V
COMMON-MODE
REJECTION RATIO CMRR
VCM
VS = 4.5 V to 18 V
RL ≥ 2 kΩ, VO = 10 V 600
RL ≥ 2 kΩ 11.5
=
10 V
94
118
4
dB
POWER SUPPLY
REJECTION RATIO PSRR
16
51
µV/V
V/mV
V
LARGE-SIGNAL
VOLTAGE GAIN
AVO
VO
1200
13.5
300
800
OUTPUT
VOLTAGE SWING
10.5
13.0
NOTES
1Input offset voltage measurements are performed by automated test equipment approximately 0.5 seconds after application of power. A/E grades guaranteed fully
warmed up.
2The TCVOS performance is within the specifications unnulled or when nulled with RP = 8 kΩ to 20 kΩ. TCVOS is 100% tested for A/E grades, sample tested for
C/F/G grades.
3Guaranteed by design.
–3–
REV. A
OP27
(@ VS = 15 V, –25ꢁC¯≤ TA ≤ 85ꢁC for OP27J, OP27Z, 0ꢁC ≤ TA ≤ 70ꢁC for OP27EP,
ELECTRICAL CHARACTERISTICS OP27FP, and –40ꢁC ≤ TA ≤ 85ꢁC for OP27GP, OP27GS, unless otherwise noted.)
OP27E
Typ
OP27F
OP27G
Parameter
Symbol Conditions
Min
Max Min
Typ Max Min Typ Max
Unit
INPUT ONSET
VOLTAGE
VOS
20
50
40
140
55
220
µV
AVERAGE INPUT
OFFSET DRIFT
1
TCVOS
0.2
0.2
0.6
0.6
0.3
0.3
1.3
1.3
0 4
0 4
1.8
1.8
µV/°C
µV/°C
2
TCVOSn
INPUT OFFSET
CURRENT
IOS
IB
10
14
50
60
14
85
95
20
135
nA
INPUT BIAS
CURRENT
18
11.8
121
25
10.5 11.8
150 nA
INPUT VOLTAGE
RANGE
IVR
10.5
10 V 110
11.8
10.5
V
COMMON-MODE
REJECTION RATIO CMRR
VCM
=
124
2
102
96
118
2
dB
POWER SUPPLY
REJECTION RATIO PSRR
VS = 4.5 V
to 18 V
15
2
16
32
µV/V
LARGE-SIGNAL
VOLTAGE GAIN
AVO
RL ≥ 2 kΩ,
VO = 10 V
750
11.7
1500
13.6
700
1300
13.5
450
1000
V/mV
V
OUTPUT
VOLTAGE SWING
VO
RL ≥ 2 kΩ
11.4
11.0 13.3
NOTES
1The TCVOS performance is within the specifications unnulled or when nulled with RP = 8 kΩ to 20 kΩ. TCVOS is 100% tested for A/E grades, sample tested for
C/F/G grades.
2Guaranteed by design.
–4–
REV. A
OP27
DICE CHARACTERISTICS
1. NULL
2. (–) INPUT
3. (+) INPUT
4. V–
6. OUTPUT
7. V+
8. NULL
DIE SIZE 0.109 ꢂ 0.055 INCH, 5995 SQ. MILS
(2.77 ꢂ 1.40mm, 3.88 SQ. mm)
(@ VS = 15 V, TA = 25ꢁC unless otherwise noted.)
WAFER TEST LIMITS
OP27N
Limit
OP27G
Limit
OP27GR
Limit
Parameter
Symbol
Conditions
Unit
INPUT OFFSET VOLTAGE*
INPUT OFFSET CURRENT
INPUT BIAS CURRENT
VOS
IOS
IB
35
35
40
11
60
50
55
11
100
75
µV Max
nA Max
nA Max
V Min
80
INPUT VOLTAGE RANGE
IVR
11
COMMON-MODE REJECTION
RATIO
CMRR
PSRR
V
CM = IVR
114
10
106
10
100
20
dB Min
POWER SUPPLY
VS = 4 V to 18 V
µV/V Max
LARGE-SIGNAL VOLTAGE
GAIN
AVO
AVO
RL ≥ 2 kΩ, VO = 10 V
RL ≥ 600 Ω, VO = 10 V
1000
800
1000
800
700
600
V/mV Min
V/mV Min
OUTPUT VOLTAGE SWING
VO
VO
RL ≥ 2 kΩ
RL2600n
12.0
10.0
12.0
10.0
+11.5
10.0
V Min
V Min
POWER CONSUMPTION
Pd
VO = 0
140
140
170
mW Max
NOTE
*Electrical tests are performed at wafer probe to the limits shown. Due to variations in assembly methods and normal yield loss, yield after packaging is not guaranteed
for standard product dice. Consult factory to negotiate specifications based on dice lot qualification through sample lot assembly and testing.
–5–
REV. A
OP27
(@ V = 15 V, T = 25ꢁC unless otherwise noted.)
TYPICAL ELECTRICAL CHARACTERISTICS
S
A
OP27N
Typical
OP27G
Typical
OP27GR
Typical
Parameter
Symbol
Conditions
Unit
AVERAGE INPUT OFFSET
VOLTAGE DRIFT*
TCVOS or
TCVOSn
Nulled or Unnulled
RP = 8 kΩ to 20 kΩ
0.2
0.3
0.4
µV/°C
AVERAGE INPUT OFFSET
CURRENT DRIFT
TCIOS
TCIB
80
130
160
180
200
pA/°C
pA/°C
AVERAGE INPUT BIAS
CURRENT DRIFT
100
INPUT NOISE VOLTAGE
DENSITY
en
en
en
fO = 10 Hz
fO = 30 Hz
fO = 1000 Hz
3.5
3.1
3.0
3.5
3.1
3.0
3.8
3.3
3.2
nV/√Hz
nV/√Hz
nV/√Hz
INPUT NOISE CURRENT
DENSITY
in
in
in
fO = 10 Hz
fO = 30 Hz
fO = 1000 Hz
1.7
1.0
0.4
1.7
1.0
0.4
1.7
1.0
0.4
pA/√Hz
pA/√Hz
pA/√Hz
INPUT NOISE VOLTAGE
SLEW RATE
enp-p
SR
0.1 Hz to 10 Hz
RL ≥ 2 kΩ
0.08
2.8
0.08
2.8
0.09
2.8
µV p-p
V/µs
GAIN BANDWIDTH
PRODUCT
GBW
8
8
8
MHz
NOTE
*Input offset voltage measurements are performed by automated test equipment approximately 0.5 seconds after application of power.
–6–
REV. A
OP27
(Continued from page 1)
The OP27 provides excellent performance in low-noise, high-
accuracy amplification of low-level signals. Applications include
stable integrators, precision summing amplifiers, precision voltage-
threshold detectors, comparators, and professional audio circuits
such as tape-head and microphone preamplifiers.
PSRR and CMRR exceed 120 dB. These characteristics, coupled
with long-term drift of 0.2 µV/month, allow the circuit designer
to achieve performance levels previously attained only by dis-
crete designs.
The OP27 is a direct replacement for 725, OP06, OP07, and
OP45 amplifiers; 741 types may be directly replaced by remov-
ing the 741’s nulling potentiometer.
Low-cost, high-volume production of OP27 is achieved by
using an on-chip Zener zap-trimming network. This reliable
and stable offset trimming scheme has proved its effectiveness
over many years of production history.
ABSOLUTE MAXIMUM RATINGS4
3
Package Type
ꢃJA
ꢃJC
Unit
Supply Voltage . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
22 V
22 V
Input Voltage1 . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
TO 99 (J)
150
18
16
43
38
43
°C/W
°C/W
°C/W
°C/W
°C/W
8-Lead Hermetic DlP (Z) 148
Output Short-Circuit Duration . . . . . . . . . . . . . . . . Indefinite
Differential Input Voltage2 . . . . . . . . . . . . . . . . . . . . . . 0.7 V
Differential Input Current2 . . . . . . . . . . . . . . . . . . . . 25 mA
Storage Temperature Range . . . . . . . . . . . . –65°C to +150°C
Operating Temperature Range
OP27A, OP27C (J, Z) . . . . . . . . . . . . . . . . –55°C to +125°C
OP27E, OP27F (J, Z) . . . . . . . . . . . . . . . . . –25°C to +85°C
OP27E, OP27F (P) . . . . . . . . . . . . . . . . . . . . . . 0°C to 70°C
OP27G (P, S, J, Z) . . . . . . . . . . . . . . . . . . –40°C to +85°C
Lead Temperature Range (Soldering, 60 sec) . . . . . . . 300°C
Junction Temperature . . . . . . . . . . . . . . . . . –65°C to +150°C
8-Lead Plastic DIP (P)
20-Contact LCC (RC)
8-Lead SO (S)
103
98
158
NOTES
1For supply voltages less than 22 V, the absolute maximum input voltage is
equal to the supply voltage.
2The OP27’s inputs are protected by back-to-back diodes. Current limiting
resistors are not used in order to achieve low noise. If differential input voltage
exceeds 0.7 V, the input current should be limited to 25 mA.
JA is specified for worst-case mounting conditions, i.e., JA is specified for
device in socket for TO, CERDIP, and P-DIP packages; JA is specified for
device soldered to printed circuit board for SO package.
4Absolute Maximum Ratings apply to both DICE and packaged parts, unless
otherwise noted.
3
ORDERING INFORMATION1
Package
TA = 25°C
OS Max
(µV)
Operating
Temperature
Range
V
CERDIP
8-Lead
Plastic
8-Lead
TO-99
25
25
60
100
100
100
OP27AJ2, 3
OP27AZ2
OP27EZ
MIL
OP27EJ2, 3
OP27EP
OP27FP3
IND/COM
IND/COM
MIL
XIND
XIND
OP27CZ3
OP27GZ
OP27GJ
OP27GP
OP27GS4
NOTES
1Burn-in is available on commercial and industrial temperature range parts in CERDIP, plastic
DIP, and TO-can packages.
2For devices processed in total compliance to MIL-STD-883, add /883 after part number.
Consult factory for 883 data sheet.
3Not for new design; obsolete April 2002.
4For availability and burn-in information on SO and PLCC packages, contact your local
sales office.
CAUTION
ESD (electrostatic discharge) sensitive device. Electrostatic charges as high as 4000 V readily
accumulate on the human body and test equipment and can discharge without detection. Although
the OP27 features proprietary ESD protection circuitry, permanent damage may occur on devices
subjected to high-energy electrostatic discharges. Therefore, proper ESD precautions are
recommended to avoid performance degradation or loss of functionality.
WARNING!
ESD SENSITIVE DEVICE
REV. A
–7–
OP27
–Typical Performance Characteristics
10
9
100
90
80
70
60
50
100
10
1
T
V
= 25ꢁC
= ꢄ15V
A
8
7
6
S
741
5
4
I/F CORNER
LOW NOISE
3
I/F CORNER =
2.7Hz
AUDIO OP AMP
OP27
I/F CORNER
I/F CORNER = 2.7Hz
2
TEST TIME OF 10sec FURTHER
LIMITS LOW FREQUENCY
(<0.1Hz) GAIN
INSTRUMENTATION AUDIO RANGE
40
RANGETO DC
TO 20kHz
1
30
0.01
1
10
100
1k
0.1
1
10
100
1
10
100
1k
FREQUENCY – Hz
FREQUENCY – Hz
FREQUENCY – Hz
TPC 1. 0.1 Hz to 10 Hzp-p Noise Tester
Frequency Response
TPC 2. Voltage Noise Density vs.
Frequency
TPC 3. A Comparison of Op Amp
Voltage Noise Spectra
100
10
5
R1
R2
T
V
= 25ꢁC
= ꢄ15V
A
T
V
= 25ꢁC
= ꢄ15V
V
= ꢄ15V
A
S
S
S
R
– 2R1
4
3
2
1
S
AT 10Hz
AT 1kHz
1
10
0.1
AT 10Hz
AT 1kHz
RESISTOR NOISE ONLY
1
100
0.01
100
–50 –25
0
25
50
75
100 125
1k
10k
1k
10k
100k
TEMPERATURE – ꢁC
SOURCE RESISTANCE –ꢅ
BANDWIDTH – Hz
TPC 4. Input Wideband Voltage
Noise vs. Bandwidth (0.1 Hz to
Frequency Indicated)
TPC 5. Total Noise vs. Sourced
Resistance
TPC 6. Voltage Noise Density vs.
Temperature
5
10.0
5.0
4.0
T
= 25ꢁC
A
4
3
2
1
AT 10Hz
AT 1kHz
T
= +125ꢁC
A
1.0
3.0
2.0
1.0
T
= –55ꢁC
A
T
= +25ꢁC
A
I/F CORNER = 140Hz
0.1
10
0
10
20
30
40
5
15
25
35
45
100
1k
10k
TOTAL SUPPLYVOLTAGE –V
TOTAL SUPPLYVOLTAGE (V+ – V–) –V
FREQUENCY – Hz
TPC 7. Voltage Noise Density vs.
Supply Voltage
TPC 8. Current Noise Density vs.
Frequency
TPC 9. Supply Current vs. Supply
Voltage
–8–
REV. A
OP27
60
50
40
6
4
OP27C
OP27A
T
V
= 25ꢁC
= 15V
A
S
2
10
30
20
0
–2
–4
OP27 C/G
OP27 F
10
0
OP27A
OP27A
–6
6
–10
–20
–30
5
4
OP27 A/E
2
–40
0
TRIMMINGWITH
10kꢅ POT DOES
NOT CHANGE
–2
–50
–60
–70
–4
–6
TCV
OS
OP27C
1
0
1
2
3
4
5
–75 –50 –25
0
25 50 75 100 125 150 175
0
1
2
3
4
5
6
7
TEMPERATURE – ꢁC
TIME AFTER POWER ON – Min
TIME – Months
TPC 10. Offset Voltage Drift of
Five Representative Units vs.
Temperature
TPC 11. Long-Term Offset Voltage
Drift of Six Representative Units
TPC 12. Warm-Up Offset Voltage
Drift
50
50
30
V
= ꢄ15V
V
= ꢄ15V
V = ꢄ15V
S
S
S
25
20
40
30
20
10
40
30
20
T
25ꢁC
=
T = 70ꢁC
A
A
15
10
5
THERMAL
SHOCK
RESPONSE
BAND
OP27C
OP27A
OP27C
10
0
DEVICE IMMERSED
IN 70ꢁC OIL BATH
OP27A
25
0
–20
0
–75 –50 –25
0
50 75 100 125
–50 –25
0
25 50 75 100 125 150
0
20
40
100
60
80
TEMPERATURE – ꢁC
TEMPERATURE – ꢁC
TIME – Sec
TPC 13. Offset Voltage Change Due
to Thermal Shock
TPC 14. Input Bias Current vs.
Temperature
TPC 15. Input Offset Current vs.
Temperature
130
110
25
80
T
V
= 25ꢁC
= ꢄ15V
A
10
9
ꢆ
S
70
100
120
140
160
180
200
220
20
15
10
5
ꢆM
GAIN
V
S
= ꢄ15V
90
70
60
PHASE
MARGIN
= 70ꢁ
GBW
SLEW
25
50
4
8
7
6
50
30
0
3
2
10
–5
–10
–10
1
10 100 1k 10k 100k 1M 10M 100M
–75 –50 –25
0
50
75 100 125
1M
10M
FREQUENCY – Hz
100M
FREQUENCY – Hz
TEMPERATURE – ꢁC
TPC 16. Open-Loop Gain vs.
Frequency
TPC 17. Slew Rate, Gain-Bandwidth
Product, Phase Margin vs.
Temperature
TPC 18. Gain, Phase Shift vs.
Frequency
–9–
REV. A
OP27
2.5
28
24
20
16
12
8
18
16
T
V
= 25ꢁC
= ꢄ15V
A
T
= 25ꢁC
A
S
POSITIVE
SWING
14
12
10
8
2.0
1.5
1.0
0.5
R
= 2kꢅ
L
NEGATIVE
SWING
R
= 1kꢅ
L
6
4
2
T
V
= 25ꢁC
= ꢄ15V
4
A
0
S
–2
100
0
1k
0
0
10
20
30
40
50
1k
10k
10k
100k
1M
10M
LOAD RESISTANCE – ꢅ
TOTAL SUPPLYVOLTAGE –V
FREQUENCY – Hz
TPC 19. Open-Loop Voltage Gain vs.
Supply Voltage
TPC 20. Maximum Output Swing vs.
Frequency
TPC 21. Maximum Output Voltage
vs. Load Resistance
100
V
= ꢄ15V
= 100mV
= +1
S
V
IN
500ns
= +1
2V
2ꢀs
20mV
A
80
60
40
20
0
V
50mV
0V
+5V
0V
A
A
= +1
VCL
VCL
C
V
= 15pF
= ꢄ15V
= 25ꢁC
V
T
= ꢄ15V
= 25ꢁC
L
S
S
A
A
T
–50mV
–5V
0
500
1000
1500
2000
2500
CAPACITIVE LOAD – pF
TPC 22. Small-Signal Overshoot vs.
Capacitive Load
TPC 23. Small-Signal Transient
Response
TPC 24. Large-Signal Transient
Response
60
140
16
V
T
= ꢄ15V
= 25ꢁC
= ꢄ10V
T
V
= 25ꢁC
= ꢄ15V
S
A
T = –55ꢁC
A
12
8
A
S
V
T
= +25ꢁC
CM
A
50
40
30
20
10
120
100
80
T
= +125ꢁC
A
4
I
(+)
SC
0
T
= –55ꢁC
A
–4
–8
–12
–16
I
(–)
SC
T
= +25ꢁC
A
T
= +125ꢁC
ꢄ10
A
60
100
0
1
2
3
4
5
0
ꢄ5
ꢄ15
ꢄ20
1k
10k
100k
1M
FREQUENCY – Hz
TIME FROM OUTPUT SHORTEDTO
SUPPLYVOLTAGE –V
GROUND – Min
TPC 27. Common-Mode Input Range
vs. Supply Voltage
TPC 25. Short-Circuit Current vs.
Time
TPC 26. CMRR vs. Frequency
–10–
REV. A
OP27
2.4
2.2
2.0
1.8
1.6
1.4
1.2
1.0
0.8
0.1ꢀF
T
V
= 25ꢁC
= ꢄ15V
A
S
100kꢅ
1 SEC/DIV
120
80
OP27
D.U.T.
10ꢅ
40
2kꢅ
0
VOLTAGE
GAIN
22ꢀF
4.3kꢅ
2.2ꢀF
–40
–90
–120
OP12
100kꢅ
= 50,000
SCOPE ꢂ 1
= 1Mꢅ
R
IN
4.7ꢀF
0.6
0.4
110kꢅ
0.1ꢀF
24.3kꢅ
0.1Hz to 10Hz p-p NOISE
100
1k
10k
100k
LOAD RESISTANCE –ꢅ
TPC 28. Voltage Noise Test Circuit
(0.1 Hz to 10 Hz)
TPC 29. Open-Loop Voltage Gain vs.
Load Resistance
TPC 30. Low-Frequency Noise
160
T
= 25ꢁC
A
140
120
100
80
60
40
20
0
NEGATIVE
SWING
POSITIVE
SWING
1
10 100 1k 10k 100k 1M 10M 100M
FREQUENCY – Hz
TPC 31. PSRR vs. Frequency
APPLICATION INFORMATION
approximately (VOS/300) µV/°C. For example, the change in
TCVOS will be 0.33 µV/°C if VOS is adjusted to 100 µV. The
offset voltage adjustment range with a 10 kΩ potentiometer is
4 mV. If smaller adjustment range is required, the nulling
sensitivity can be reduced by using a smaller pot in conjuction
with fixed resistors. For example, the network below will have a
280 µV adjustment range.
OP27 series units may be inserted directly into 725 and OP07
sockets with or without removal of external compensation or
nulling components. Additionally, the OP27 may be fitted to
unnulled 741-type sockets; however, if conventional 741 nulling
circuitry is in use, it should be modified or removed to ensure
correct OP27 operation. OP27 offset voltage may be nulled to
zero (or another desired setting) using a potentiometer (see
Offset Nulling Circuit).
4.7kꢅ
1kꢅ POT
4.7kꢅ
8
1
The OP27 provides stable operation with load capacitances of
up to 2000 pF and 10 V swings; larger capacitances should be
decoupled with a 50 Ω resistor inside the feedback loop. The
OP27 is unity-gain stable.
V+
Figure 2.
Thermoelectric voltages generated by dissimilar metals at the
input terminal contacts can degrade the drift performance. Best
operation will be obtained when both input contacts are main-
tained at the same temperature.
NOISE MEASUREMENTS
To measure the 80 nV peak-to-peak noise specification of the
OP27 in the 0.1 Hz to 10 Hz range, the following precautions
must be observed:
1. The device must be warmed up for at least five minutes.
As shown in the warm-up drift curve, the offset voltage
typically changes 4 µV due to increasing chip temperature
after power-up. In the 10-second measurement interval,
these temperature-induced effects can exceed tens-of-
nanovolts.
OFFSET VOLTAGE ADJUSTMENT
The input offset voltage of the OP27 is trimmed at wafer level.
However, if further adjustment of VOS is necessary, a 10 kΩ trim
potentiometer can be used. TCVOS is not degraded (see Offset
Nulling Circuit). Other potentiometer values from 1 kΩ to 1 MΩ
can be used with a slight degradation (0.1 µV/°C to 0.2 µV/°C)
of TCVOS. Trimming to a value other than zero creates a drift of
2. For similar reasons, the device has to be well-shielded from
air currents. Shielding minimizes thermocouple effects.
–11–
REV. A
OP27
3. Sudden motion in the vicinity of the device can also
“feedthrough” to increase the observed noise.
2
1/2
Voltage Noise
+
(
)
2
Total Noise = Current Noise × R
+
(
)
S
4. The test time to measure 0.1 Hz to 10 Hz noise should not
exceed 10 seconds. As shown in the noise-tester frequency
response curve, the 0.1 Hz corner is defined by only one
zero. The test time of 10 seconds acts as an additional zero
to eliminate noise contributions from the frequency band
below 0.1 Hz.
2
Resistor Noise
(
)
Figure 4 shows noise versus source-resistance at 1000 Hz. The
same plot applies to wideband noise. To use this plot, multiply
the vertical scale by the square root of the bandwidth.
5. A noise-voltage-density test is recommended when measuring
noise on a large number of units. A 10 Hz noise-voltage-
density measurement will correlate well with a 0.1 Hz to 10 Hz
peak-to-peak noise reading, since both results are determined
by the white noise and the location of the 1/f corner frequency.
100
50
1
OP08/108
UNITY-GAIN BUFFER APPLICATIONS
2
OP07
10
When Rf ≤ 100 Ω and the input is driven with a fast, large signal
pulse (>1 V), the output waveform will look as shown in the
pulsed operation diagram (Figure 3).
1 R UNMATCHED
S
5
5534
e.g.R = R = 10kꢅ, R = 0
S
S1 S2
2 R MATCHED
S
During the fast feedthrough-like portion of the output, the input
protection diodes effectively short the output to the input and a
current, limited only by the output short-circuit protection, will
be drawn by the signal generator. With Rf ≥ 500 Ω, the output is
capable of handling the current requirements (IL ≤ 20 mA at 10 V);
the amplifier will stay in its active mode and a smooth transition
will occur.
e.g.R = 10kꢅ, R = R = 5kꢅ
S1 S2
S
OP27/37
R
S1
R
S2
REGISTER
NOISE ONLY
1
50
100
500
1k
5k
10k
50k
R
– SOURCE RESISTANCE –ꢅ
S
Figure 4. Noise vs. Source Resistance (Including Resistor
Noise) at 1000 Hz
When Rf > 2 kΩ, a pole will be created with Rf and the amplifier’s
input capacitance (8 pF) that creates additional phase shift and
reduces phase margin. A small capacitor (20 pF to 50 pF) in
parallel with Rf will eliminate this problem.
At RS <1 kΩ, the OP27’s low voltage noise is maintained. With
RS <1 kΩ, total noise increases, but is dominated by the resis-
tor noise rather than current or voltage noise. lt is only beyond
RS of 20 kΩ that current noise starts to dominate. The argument
can be made that current noise is not important for applica-
tions with low to moderate source resistances. The crossover
between the OP27, OP07, and OP08 noise occurs in the 15 kΩ to
40 kΩ region.
R
f
–
2.8V/ꢀs
OP27
Figure 5 shows the 0.1 Hz to 10 Hz peak-to-peak noise. Here
the picture is less favorable; resistor noise is negligible and current
noise becomes important because it is inversely proportional to
the square root of frequency. The crossover with the OP07
occurs in the 3 kΩ to 5 kΩ range depending on whether bal-
anced or unbalanced source resistors are used (at 3 kΩ the IB
and IOS error also can be three times the VOS spec.).
+
Figure 3. Pulsed Operation
COMMENTS ON NOISE
The OP27 is a very low-noise monolithic op amp. The outstanding
input voltage noise characteristics of the OP27 are achieved mainly
by operating the input stage at a high quiescent current. The input
bias and offset currents, which would normally increase, are held
to reasonable values by the input bias-current cancellation circuit.
The OP27A/E has IB and IOS of only 40 nA and 35 nA at 25°C
respectively. This is particularly important when the input has a
high source resistance. In addition, many audio amplifier design-
ers prefer to use direct coupling. The high IB, VOS, and TCVOS
of previous designs have made direct coupling difficult, if not
impossible, to use.
1k
OP08/108
500
5534
OP07
1
2
100
OP27/37
1 RS UNMATCHED
50
e.g.RS = RS1 = 10kꢅ, RS2 = 0
2 RS MATCHED
Voltage noise is inversely proportional to the square root of bias
current, but current noise is proportional to the square root of
bias current. The OP27’s noise advantage disappears when high
source-resistors are used. Figures 4, 5, and 6 compare OP27’s
observed total noise with the noise performance of other devices
in different circuit applications.
e.g.RS = 10kꢅ, RS1 = RS2 = 5kꢅ
RS1
RS2
REGISTER
NOISE ONLY
10
50
100
500
1k
5k
10k
50k
R
– SOURCE RESISTANCE –ꢅ
S
Figure 5. Peak-to-Peak Noise (0.1 Hz to 10 Hz) as Source
Resistance (Includes Resistor Noise)
–12–
REV. A
OP27
Therefore, for low-frequency applications, the OP07 is better
than the OP27/OP37 when RS > 3 kΩ. The only exception is
when gain error is important. Figure 6 illustrates the 10 Hz
noise. As expected, the results are between the previous two
figures.
Figure 7 is an example of a phono pre-amplifier circuit using the
OP27 for A1; R1-R2-C1-C2 form a very accurate RIAA net-
work with standard component values. The popular method to
accomplish RIAA phono equalization is to employ frequency-
dependent feedback around a high-quality gain block. Properly
chosen, an RC network can provide the three necessary time
constants of 3180, 318, and 75 µs.1
For reference, typical source resistances of some signal sources
are listed in Table I.
For initial equalization accuracy and stability, precision metal
film resistors and film capacitors of polystyrene or polypropy-
lene are recommended since they have low voltage coefficients,
dissipation factors, and dielectric absorption.4 (High-K ceramic
capacitors should be avoided here, though low-K ceramics—
such as NPO types, which have excellent dissipation factors
and somewhat lower dielectric absorption—can be considered
for small values.)
Table I.
Source
Device
Impedance
Comments
Strain Gauge
<500 Ω
Typically used in low-
frequency applications.
Magnetic
Tapehead
<1500 Ω
<1500 Ω
Low is very important to
reduce self-magnetization
problems when direct coupling
is used. OP27 IB can be
neglected.
C4 (2)
R5
220ꢀF
100kꢅ
+
+
MOVING MAGNET
CARTRIDGE INPUT
LF ROLLOFF
OUT
C3
0.47ꢀF
IN
Magnetic
Phonograph
Cartridges
Similar need for low IB in
direct coupled applications.
OP27 will not introduce any
self-magnetization problem.
A1
OP27
Ca
150pF
Ra
R4
75kꢅ
C1
0.03ꢀF
47.5kꢅ
OUTPUT
R1
97.6kꢅ
Linear Variable <1500 Ω
Differential
Transformer
Used in rugged servo-feedback
applications. Bandwidth of
interest is 400 Hz to 5 kHz.
R2
C2
0.01ꢀF
7.87kꢅ
R3
100ꢅ
G = 1kHz GAIN
Open-Loop Gain
R1
R3
1 +
= 0.101 (
)
Frequency at
OP07
OP27
OP37
= 98.677 (39.9dB) AS SHOWN
3 Hz
10 Hz
30 Hz
100 dB
100 dB
90 dB
124 dB
120 dB
110 dB
125 dB
125 dB
124 dB
Figure 7.
The OP27 brings a 3.2 nV/√Hz voltage noise and 0.45 pA/√Hz
current noise to this circuit. To minimize noise from other
sources, R3 is set to a value of 100 Ω, which generates a voltage
noise of 1.3 nV/√Hz. The noise increases the 3.2 nV/√Hz of the
amplifier by only 0.7 dB. With a 1 kΩ source, the circuit noise
measures 63 dB below a 1 mV reference level, unweighted, in a
20 kHz noise bandwidth.
For further information regarding noise calculations, see “Minimization of Noise
in Op Amp Applications,” Application Note AN-15.
100
50
1
2
Gain (G) of the circuit at 1 kHz can be calculated by the
OP08/108
expression:
R1
OP07
10
G = 0.101 1+
R3
5534
1 RS UNMATCHED
e.g.RS = RS1 = 10kꢅ, RS2 = 0
2 RS MATCHED
For the values shown, the gain is just under 100 (or 40 dB).
Lower gains can be accommodated by increasing R3, but gains
higher than 40 dB will show more equalization errors because of
the 8 MHz gain-bandwidth of the OP27.
5
e.g.RS = 10kꢅ, RS1 = RS2 = 5kꢅ
OP27/37
RS1
RS2
REGISTER
NOISE ONLY
This circuit is capable of very low distortion over its entire range,
generally below 0.01% at levels up to 7 V rms. At 3 V output
levels, it will produce less than 0.03% total harmonic distortion
at frequencies up to 20 kHz.
1
50
100
500
1k
5k
10k
50k
R
– SOURCE RESISTANCE –ꢅ
S
Figure 6. 10 Hz Noise vs. Source Resistance (Includes
Resistor Noise)
Capacitor C3 and resistor R4 form a simple –6 dB-per-octave
rumble filter, with a corner at 22 Hz. As an option, the switch-
selected shunt capacitor C4, a nonpolarized electrolytic, bypasses
the low-frequency rolloff. Placing the rumble filter’s high-pass
action after the preamp has the desirable result of discriminating
AUDIO APPLICATIONS
The following applications information has been abstracted
from a PMI article in the 12/20/80 issue of Electronic De-
sign magazine and updated.
REV. A
–13–
OP27
against the RlAA-amplified low-frequency noise components and
pickup-produced low-frequency disturbances.
noise. The rms sum of these predominant noise sources will be
about 6 nV/√Hz, equivalent to 0.9 µV in a 20 kHz noise band-
width, or nearly 61 dB below a 1 mV input signal. Measurements
confirm this predicted performance.
A preamplifier for NAB tape playback is similar to an RIAA
phono preamp, though more gain is typically demanded, along
with equalization requiring a heavy low-frequency boost. The
circuit in Figure 7 can be readily modified for tape use, as shown
by Figure 8.
C1
R1
R3
R6
5ꢀF
1kꢅ
316kꢅ
100ꢅ
–
–
0.47ꢀF
LOW IMPEDANCE
MICROPHONE INPUT
(Z = 50ꢅTO 200ꢅ)
Rp
30kꢅ
OP27/
OP37
+
R7
10kꢅ
OUTPUT
OP27
+
TAPE
HEAD
Ra
Ca
15kꢅ
R1
33kꢅ
R2
1kꢅ
R4
316kꢅ
R3 R4
=
R1 R2
R2
5kꢅ
0.01ꢀF
Figure 9.
100kꢅ
T1 = 3180ꢀs
T2 = 50ꢀs
For applications demanding appreciably lower noise, a high
quality microphone transformer-coupled preamp (Figure 10)
incorporates the internally compensated OP27. T1 is a JE-115K-E
150 Ω/15 kΩ transformer which provides an optimum source
resistance for the OP27 device. The circuit has an overall gain of
40 dB, the product of the transformer’s voltage setup and the op
amp’s voltage gain.
Figure 8.
While the tape-equalization requirement has a flat high-frequency
gain above 3 kHz (T2 = 50 µs), the amplifier need not be stabilized
for unity gain. The decompensated OP37 provides a greater
bandwidth and slew rate. For many applications, the idealized
time constants shown may require trimming of R1 and R2 to
optimize frequency response for nonideal tapehead performance
and other factors.5
C2
1800pF
R1
121ꢅ
R2
1100ꢅ
The network values of the configuration yield a 50 dB gain at
1 kHz, and the dc gain is greater than 70 dB. Thus, the worst-case
output offset is just over 500 mV. A single 0.47 µF output capaci-
tor can block this level without affecting the dynamic range.
A1
OP27
OUTPUT
T1*
The tapehead can be coupled directly to the amplifier input,
since the worst-case bias current of 80 nA with a 400 mH, 100
µ inch head (such as the PRB2H7K) will not be troublesome.
150ꢅ
R3
100ꢅ
SOURCE
*T1 – JENSEN JE – 115K – E
JENSENTRANSFORMERS
10735 BURBANK BLVD.
N. HOLLYWOOD, CA 91601
One potential tapehead problem is presented by amplifier bias-
current transients which can magnetize a head. The OP27 and
OP37 are free of bias-current transients upon power-up or power-
down. However, it is always advantageous to control the speed
of power supply rise and fall, to eliminate transients.
Figure 10.
Gain may be trimmed to other levels, if desired, by adjusting R2
or R1. Because of the low offset voltage of the OP27, the output
offset of this circuit will be very low, 1.7 mV or less, for a 40 dB
gain. The typical output blocking capacitor can be eliminated in
such cases, but is desirable for higher gains to eliminate switch-
ing transients.
In addition, the dc resistance of the head should be carefully
controlled, and preferably below 1 kS2. For this configuration,
the bias-current-induced offset voltage can be greater than the
100pV maximum offset if the head resistance is not sufficiently
controlled.
+18V
A simple, but effective, fixed-gain transformerless microphone
preamp ( Figure 9) amplifies differential signals from low imped-
ance microphones by 50 dB, and has an input impedance of 2 kΩ.
Because of the high working gain of the circuit, an OP37 helps
to preserve bandwidth, which will be 110 kHz. As the OP37
is a decompensated device (minimum stable gain of 5), a dummy
resistor, Rp, may be necessary, if the microphone is to be
unplugged. Otherwise the 100% feedback from the open input
may cause the amplifier to oscillate.
OP27
–18V
Figure 11. Burn-In Circuit
Common-mode input-noise rejection will depend upon the
match of the bridge-resistor ratios. Either close-tolerance (0.1%)
types should be used, or R4 should be trimmed for best CMRR.
All resistors should be metal film types for best stability and
low noise.
Capacitor C2 and resistor R2 form a 2 µs time constant in this
circuit, as recommended for optimum transient response by the
transformer manufacturer. With C2 in use, A1 must have unity-
gain stability. For situations where the 2 µs time constant is not
necessary, C2 can be deleted, allowing the faster OP37 to be
employed.
Noise performance of this circuit is limited more by the input
resistors R1 and R2 than by the op amp, as R1 and R2 each gen-
erate a 4 nV/√Hz noise, while the op amp generates a 3.2 nV/√Hz
–14–
REV. A
OP27
Some comment on noise is appropriate to understand the
capability of this circuit. A 150 Ω resistor and R1 and R2
gain resistors connected to a noiseless amplifier will generate
220 nV of noise in a 20 kHz bandwidth, or 73 dB below a 1 mV
reference level. Any practical amplifier can only approach this noise
level; it can never exceed it. With the OP27 and T1 specified, the
additional noise degradation will be close to 3.6 dB (or –69.5 refer-
enced to 1 mV).
References
1. Lipshitz, S.R, “On RIAA Equalization Networks,” JAES,
Vol. 27, June 1979, p. 458–481.
2. Jung, W.G., IC Op Amp Cookbook, 2nd. Ed., H.W. Sams and
Company, 1980.
3. Jung, W.G., Audio IC Op Amp Applications, 2nd. Ed., H.W.
Sams and Company, 1978.
R
10kꢅ
4. Jung, W.G., and Marsh, R.M., “Picking Capacitors,” Audio,
P
February and March, 1980.
V+
5. Otala, M., “Feedback-Generated Phase Nonlinearity in
Audio Amplifiers,” London AES Convention, March 1980,
preprint 1976.
OP27
INPUT
OUTPUT
6. Stout, D.F., and Kautman, M., Handbook of Operational
Amplifier Circuit Design, New York, McGraw-Hill, 1976.
V–
Figure 12. Offset Nulling Circuit
OUTLINE DIMENSIONS
Dimensions shown in inches and (mm).
8-Lead PDIP Package (P-Suffix)
(N-8)
8-Lead SOIC Package (S-Suffix)
(R-8)
0.430 (10.92)
0.348 (8.84)
0.1968 (5.00)
0.1890 (4.80)
8
5
8
1
5
4
0.280 (7.11)
0.240 (6.10)
0.2440 (6.20)
0.2284 (5.80)
0.1574 (4.00)
0.1497 (3.80)
1
4
0.325 (8.25)
0.300 (7.62)
PIN 1
PIN 1
0.100 (2.54)
BSC
0.0196 (0.50)
0.0099 (0.25)
0.0500 (1.27)
BSC
ꢂ 45ꢁ
0.060 (1.52)
0.015 (0.38)
0.210
(5.33)
MAX
0.195 (4.95)
0.115 (2.93)
0.0688 (1.75)
0.0532 (1.35)
0.0098 (0.25)
0.0040 (0.10)
0.130
(3.30)
MIN
8ꢁ
0ꢁ
0.160 (4.06)
0.115 (2.93)
0.0500 (1.27)
0.0160 (0.41)
0.0192 (0.49)
0.0138 (0.35)
0.0098 (0.25)
0.0075 (0.19)
SEATING
PLANE
0.015 (0.381)
0.008 (0.204)
0.022 (0.558) 0.070 (1.77) SEATING
0.014 (0.356) 0.045 (1.15)
PLANE
8-Pin (TO-99) Header Package (J-Suffix)
(H-8A)
8-Lead CERDIP Package (Z-Suffix)
(Q-8)
REFERENCE PLANE
0.750 (19.05)
0.005 (0.13) 0.055 (1.4)
MIN
MAX
0.500 (12.70)
0.185 (4.70)
0.165 (4.19)
8
5
0.250 (6.35) MIN
0.100 (2.54) BSC
0.310 (7.87)
0.220 (5.59)
0.160 (4.06)
0.110 (2.79)
0.050 (1.27) MAX
PIN 1
5
1
4
4
6
8
0.045 (1.14)
0.027 (0.69)
0.100 (2.54)
0.200
(5.08)
BSC
BSC
0.320 (8.13)
0.290 (7.37)
3
7
0.405 (10.29) MAX
0.060 (1.52)
0.015 (0.38)
2
0.200 (5.08)
MAX
1
0.100
0.019 (0.48)
0.016 (0.41)
(2.54)
BSC
0.150
(3.81)
MIN
0.200 (5.08)
0.125 (3.18)
0.034 (0.86)
0.027 (0.69)
0.040 (1.02) MAX
0.021 (0.53)
0.016 (0.41)
0.045 (1.14)
0.010 (0.25)
0.015 (0.38)
0.008 (0.20)
SEATING
PLANE
45 BSC
15
0
0.023 (0.58) 0.070 (1.78)
0.014 (0.36) 0.030 (0.76)
BASE & SEATING PLANE
REV. A
–15–
Revision History
Location
Page
9/01—Data Sheet changed from REV. 0 to REV. A.
Edits to ORDERING INFORMATION . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1
Edits to PIN CONNECTIONS . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1
Edits to ABSOLUTE MAXIMUM RATINGS . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 2
Edits to PACKAGE TYPE . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 2
Edits to ELECTRICAL CHARACTERISTICS . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 2, 3
Edits to WAFER TEST LIMITS . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 4
Deleted TYPICAL ELECTRICAL CHARACTERISTICS . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 4
Edits to BURN-IN CIRCUIT figure . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 7
Edits to APPLICATION INFORMATION . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 8
–16–
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