OP37EZ [ADI]
Low Noise, Precision, High Speed Operational Amplifier; 低噪声，精密，高速运算放大器
| 型号： | OP37EZ |
| 厂家： | 
ADI |
| 描述： | Low Noise, Precision, High Speed Operational Amplifier |
| 文件： | 总16页 (文件大小：385K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
Low Noise, Precision, High Speed
a
>
Operational Amplifier (A VCL 5)
OP37
FEATURES
The output stage has good load driving capability. A guaranteed
swing of 10 V into 600 Ω and low output distortion make the
OP37 an excellent choice for professional audio applications.
Low Noise, 80 nV p-p (0.1 Hz to 10 Hz)
3 nV/√Hz @ 1 kHz
Low Drift, 0.2 V/؇C
High Speed, 17 V/s Slew Rate
63 MHz Gain Bandwidth
Low Input Offset Voltage, 10 V
Excellent CMRR, 126 dB (Common-Voltage @ 11 V)
High Open-Loop Gain, 1.8 Million
Replaces 725, OP-07, SE5534 In Gains > 5
Available in Die Form
PSRR and CMRR exceed 120 dB. These characteristics, coupled
with long-term drift of 0.2 µV/month, allow the circuit designer
to achieve performance levels previously attained only by
discrete designs.
Low-cost, high-volume production of the OP37 is achieved by
using on-chip zener-zap trimming. This reliable and stable offset
trimming scheme has proved its effectiveness over many years of
production history.
GENERAL DESCRIPTION
The OP37 brings low-noise instrumentation-type performance to
such diverse applications as microphone, tapehead, and RIAA
phono preamplifiers, high-speed signal conditioning for data
acquisition systems, and wide-bandwidth instrumentation.
The OP37 provides the same high performance as the OP27,
but the design is optimized for circuits with gains greater than
five. This design change increases slew rate to 17 V/µs and
gain-bandwidth product to 63 MHz.
PIN CONNECTIONS
The OP37 provides the low offset and drift of the OP07
plus higher speed and lower noise. Offsets down to 25 µV and
drift of 0.6 µV/°C maximum make the OP37 ideal for preci-
sion instrumentation applications. Exceptionally low noise
(en= 3.5 nV/ @ 10 Hz), a low 1/f noise corner frequency of
2.7 Hz, and the high gain of 1.8 million, allow accurate
high-gain amplification of low-level signals.
8-Lead Hermetic DIP
(Z Suffix)
Epoxy Mini-DIP
(P Suffix)
8-Lead SO
(S Suffix)
The low input bias current of 10 nA and offset current of 7 nA
are achieved by using a bias-current cancellation circuit. Over
the military temperature range this typically holds IB and IOS
to 20 nA and 15 nA respectively.
1
2
3
4
8
7
6
5
V
TRIM
V
TRIM
–IN
+IN
V–
OS
OS
OP37
V+
OUT
NC
NC = NO CONNECT
SIMPLIFIED SCHEMATIC
V+
C2
R3
R4
1
8
Q6
Q22
Q46
C1
V
ADJ.
OS
R23 R24
Q24
R1*
R2*
Q21
Q23
R9
R12
Q20 Q19
OUTPUT
Q1A Q1B
Q2B Q2A
NON-INVERTING
INPUT (+)
C3
C4
R5
Q3
Q26
INVERTING
INPUT (–)
Q45
Q11 Q12
Q27
Q28
*R1 AND R2 ARE PERMANENTLY
ADJUSTED ATWAFERTEST FOR
MINIMUM OFFSETVOLTAGE.
V–
REV. A
Information furnished by Analog Devices is believed to be accurate and
reliable. However, no responsibility is assumed by Analog Devices for its
use, norforanyinfringementsofpatentsorotherrightsofthirdpartiesthat
may result from its use. No license is granted by implication or otherwise
under any patent or patent rights of Analog Devices.
One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A.
Tel: 781/329-4700
Fax: 781/326-8703
www.analog.com
© Analog Devices, Inc., 2002
OP37
ABSOLUTE MAXIMUM RATINGS4
ORDERING GUIDE
Supply Voltage . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 22 V
Internal Voltage (Note 1 ) . . . . . . . . . . . . . . . . . . . . . . . . . 22 V
Output Short-Circuit Duration . . . . . . . . . . . . . . . . . Indefinite
Differential Input Voltage (Note2) . . . . . . . . . . . . . . . . . 0.7 V
Differential Input Current (Note 2) . . . . . . . . . . . . . . . . 25 mA
Storage Temperature Range . . . . . . . . . . . . . –65°C to +150°C
Operating Temperature Range
TA = 25°C
VOS MAX
(µV)
Operating
Temperature
Range
CerDIP
8-Lead
Plastic
8-Lead
25
25
60
100
100
OP37AZ*
OP37EZ
MIL
OP37EP
OP37FP*
OP37GP
OP37GS
IND/COM
IND/COM
XIND
OP37A . . . . . . . . . . . . . . . . . . . . . . . . . . . –55°C to +1 25°C
OP37E (Z) . . . . . . . . . . . . . . . . . . . . . . . . . . –25°C to +85°C
OP37E, OP-37F (P) . . . . . . . . . . . . . . . . . . . . . 0°C to 70°C
OP37G (P, S, Z) . . . . . . . . . . . . . . . . . . . . . –40°C to +85°C
Lead Temperature Range (Soldering, 60 sec) . . . . . . . . 300°C
Junction Temperature . . . . . . . . . . . . . . . . . . –45°C to +150°C
3
OP37GZ
XIND
*Not for new design, obsolete, April 2002.
Package Type
Unit
JA
JC
8-Lead Hermetic DIP (Z) 148
16
43
43
°C/W
°C/W
°C/W
8-Lead Plastic DIP (P)
8-Lead SO (S)
103
158
NOTES
1For supply voltages less than 22 V, the absolute maximum input voltage is equal
to the supply voltage.
2The OP37’s inputs are protected by back-to-back diodes. Current limiting resistors
are not used in order to achieve low noise. If differential input voltage exceeds 0.7 V,
the input Current should be limited to 25 mA.
3
JA is specified for worst case mounting conditions, i.e., JA is specified for device
in socket for TO, CerDIP, P-DIP, and LCC packages; JA is specified for device
soldered to printed circuit board for SO package.
4Absolute maximum ratings apply to both DICE and packaged parts, unless
otherwise noted.
CAUTION
ESD (electrostatic discharge) sensitive device. Electrostatic charges as high as 4000 V readily
accumulate on the human body and test equipment and can discharge without detection. Although
the OP37 features proprietary ESD protection circuitry, permanent damage may occur on
devices subjected to high-energy electrostatic discharges. Therefore, proper ESD precautions
are recommended to avoid performance degradation or loss of functionality.
WARNING!
ESD SENSITIVE DEVICE
–2–
REV. A
OP37
SPECIFICATIONS ( VS = ꢀ15 V, TA = 25ꢁC, unless otherwise noted.)
OP37A/E
OP37F
Min Typ Max
OP37G
Min Typ Max
Parameter
Symbol
Conditions
Min Typ Max
Unit
Input Offset
Voltage
Long-Term
Stability
Input Offset
Current
Input Bias
Current
VOS
Note 1
10
0.2
7
25
1.0
35
20
0.3
9
60
1.5
50
30
0.4
12
100
2.0
75
µV
VOS/Time Notes 2, 3
µV/Mo
nA
IOS
IB
enp-p
10
40
12
55
15
80
nA
Input Noise
Voltage
Input Noise
1 Hz to 10 Hz3, 5
0.08 0.18
0.08 0.18
0.09 0.25
µV p-p
Voltage Density en
fO = 10 Hz3
fO = 30 Hz3
fO = 1000 Hz3
3.5
3.1
3.0
5.5
4.5
3.8
3.5
3.1
3.0
5.5
4.5
3.8
3.8
3.3
3.2
8.0
5.6
4.5
nV/√ Hz
pA/√ Hz
Input Noise
CurrentDensity iN
fO = 10 Hz3, 6
1.7
1.0
0.4
4.0
2.3
0.6
1.7
1.0
0.4
4.0
2.3
0.6
1.7
1.0
0.4
f
O = 30 Hz3, 6
fO = 1000 Hz3, 6
0.6
Input Resistance
Differential
Mode
RIN
Note 7
1.3
6
3
0.9
4 5
2.5
0.7
4
2
MΩ
GΩ
V
Input Resistance
Common Mode
Input Voltage
Range
Common Mode
Rejection Ratio
Power Supply
Rejection Ratio
RINCM
IVR
11
114
12.3
11
106
12.3
11
12.3
CMRR
PSSR
VCM
=
11 V
126
1
123
1
100
120
2
dB
VS = 4 V
to 18 V
10
10
20
µV/ V
Large Signal
Voltage Gain
AVO
RL ≥ 2 kΩ,
VO = 10 V
RL ≥ 1 kΩ,
Vo = 10 V
RL ≥ 600 Ω,
1000 1800
1000 1800
700
400
1500
1500
V/m V
V/m V
800
1500
800
1500
VO
= 1 V,
VS 44
250
700
250
700
200
500
V/m V
Output Voltage
Swing
VO
RL ≥ 2 kΩ
RL ≥ 600 Ω
RL ≥ 2k Ω4
12.0 13.8
10 11.5
11 17
12.0 13.8
10 11.5
11 17
11.5 13.5
10 11.5
11 17
V
V
V/µs
Slew Rate
Gain Bandwidth
Product
SR
GBW
f
O = 10 kHz4
45
63
40
45
63
40
45
63
40
MHz
MHz
fO = 1 MHz
VO = 0, IO = 0
VO = 0
Open-Loop
Output Resistance RO
Power
Consumption
Offset Adjustment
Range
70
90
4
70
90
4
70
100
4
Ω
Pd
140
140
170
mW
mV
RP = 10 kΩ
NOTES
1Input offset voltage measurements are performed by automated test equipment approximately 0.5 seconds after application of power. A/E grades guaranteed fully
warmed up.
2Long term input offset voltage stability refers to the average trend line of VOS vs. Time over extended periods after the first 30 days of operation. Excluding the initial
hour of operation, changes in VOS during the first 30 days are typically 2.5 µV—refer to typical performance curve.
3Sample tested.
4Guaranteed by design.
5See test circuit and frequency response curve for 0.1 Hz to 10 Hz tester.
6See test circuit for current noise measurement.
7Guaranteed by input bias current.
–3–
REV. A
OP37–SPECIFICATIONS
Electrical Characteristics ( VS = ꢀ15 V, –55ꢁC < TA < +125ꢁC, unless otherwise noted.)
OP37A
Typ
OP37C
Parameter
Symbol
Conditions
Min
Max
Min
Typ
Max
Unit
Input Offset
Voltage
Average Input
Offset Drift
VOS
Note 1
1025
30
100
µV
TCVOS
TCVOSN
Note 2
Note 3
0.2
0.6
60
0.4
135
35
1.8
nA
µV/°C
Input Offset
Current
Input Bias
IOS
1550
20
30
Current
IB
150
nA
V
Input Voltage
Range
Common Mode
Rejection Ratio
Power Supply
Rejection Ratio
IVR
CMRR
PSRR
10.3
11.5
122
10.2 11.5
116
VCM
=
10 V
108
94
4
dB
VS = 4.5 V to
18 V
2 16
51
µV/ V
Large-Signal
Voltage Gain
AVO
VO
RL ≥ 2 kΩ,
VO
=
10 V
600
1200
13.5
300
10.5
800
13.0
V/m V
V
Output Voltage
Swing
RL ≥ 2 kΩ
11.5
Electrical Characteristics (V = ꢀ15 V, –25ꢁC < T < +85ꢁC for OP37EZ/FZ, 0ꢁC < T < 70ꢁC for OP37EP/FP, and –40ꢁC < T
< +85ꢁC for OP37GP/GS/GZ, unless otherwise noted.)
S
A
A
A
OP37E
Min Typ Max
OP37F
Min Typ Max
OP37C
Parameter
Symbol
Conditions
Min Typ Max
Unit
Input Offset
Voltage
Average Input
Offset Drift
VOS
20
50
40
140
55
220
µV
TCVOS
TCVOSN
Note 2
Note 3
0.2
10
0.6
50
0.3
14
1.3
85
95
0.4
20
1.8
µV/°C
nA
Input Offset
Current
Input Bias
Current
Input Voltage
Range
IOS
IB
135
14
10.5 11.8
60
18
10.5 11.8
25
10.5 11.8
150
nA
IVR
V
Common Mode
Rejection Ratio CMRR
Power Supply
Rejection Ratio PSRR
VCM
=
10 V
108
122
2
100
119
2
94
116
4
dB
VS = 4.5 V to
18 V
15
16
32
µV/ V
Large-Signal
Voltage Gain
AVO
VO
RL ≥ 2 kΩ,
VO
=
10 V
750
1500
700
1300
450
11
1000
13.3
V/mV
V
Output Voltage
Swing
RL ≥ 2 kΩ
11.7 13.6
11.4 13.5
NOTES
1Input offset voltage measurements are performed by automated test equipment approximately 0.5 seconds after application of power. A/E grades guaranteed fully
warmed up.
2The TC VOS performance is within the specifications unnulled or when nulled withRP = 8 kΩ to 20 kΩ. TC VOS is 100% tested for A/E grades, sample tested for F/G grades.
3Guaranteed by design.
–4–
REV. A
OP37
1. NULL
2. (–) INPUT
3. (+) INPUT
4. V–
6. OUTPUT
7. V+
8. NULL
(VS = ꢀ15 V, TA = 25ꢁC for OP37N, OP37G, and OP37GR devices; TA = 125ꢁC for OP37NT and OP37GT devices,
unless otherwise noted.)
Wafer Test Limits
OP37NT
Limit
OP37N
Limit
OP37GT
Limit
OP37G
Limit
OP37GR
Limit
Parameter
Symbol
Conditions
Unit
Input Offset
Voltage
Input Offset
Current
Input Bias
Current
Input Voltage
Range
Common Mode
Rejection Ratio CMRR
VOS
IOS
IB
Note 1
60
35
35
200
85
60
100
75
µV MAX
nA MAX
nA MAX
V MIN
50
50
60
40
11
114
95
55
11
106
80
IVR
10.3
10.3
100
11
VCM
=
11 V 108
100
dB MIN
Power Supply
Rejection Ratio PSRR
TA = 25°C,
VS = 4 V to
18 V
10
10
10
10
20
µV/V MAX
µV/V MAX
TA = 125°C,
VS = 4.5 V to
18 V
16
20
Large-Signal
Voltage Gain
AVO
RL ≥ 2 kΩ,
VO
=
10 V
600
1000
800
500
1000
800
700
V/mV MIN
V/mV MIN
RL ≥ 1 kΩ,
VO 10 V
=
Output Voltage
Swing
VO
Pd
RL ≥ 2 kΩ
11.5
12
10
11
12
10
11.5
10
V MIN
V MIN
RL ≥ 600 kΩ
Power
Consumption
VO = 0
140
140
170
mW MAX
NOTES
For 25°C characterlstics of OP37NT and OP37GT devices, see OP37N and OP37G characteristics, respectively.
Electrical tests are performed at wafer probe to the limits shown. Due to variations in assembly methods and normal yield loss, yield after packaging is not guaranteed
for standard product dice. Consult factory to negotiate specifications based on dice lot qualification through sample lot assembly and testing.
REV. A
–5–
OP37
(V = ꢀ15 V, T = 25ꢁC, unless otherwise noted.)
Typical Electrical Characteristics
S
A
OP37NT
Typical
OP37N
Typical
OP37GT
Typical
OP37G
Typical
OP37GR
Typical
Parameter
Symbol
Conditions
Unit
Average Input
Offset Voltage
Drift
TCVOS or Nulled or
TCVOSN
Unnulled
RP = 8 kΩ
to 20 kΩ
0.2
80
0.2
80
0.3
0.3
0.4
µV/°C
pA/°C
pA/°C
Average Input
Offset Current
Drift
Average Input
Bias Current
Drift
TCIOS
TCIB
130
160
130
160
180
200
100
100
Input Noise
Voltage Density en
fO = 10 Hz
fO = 30 Hz
3.5
3.1
3.0
3.5
3.1
3.0
3.5
3.1
3.0
3.5
3.1
3.0
3.8
3.3
3.2
nV/√Hz
nV/√Hz
nV/√Hz
f
O = 1000 Hz
Input Noise
Current Density in
fO = 10 Hz
fO = 30 Hz
1.7
1.0
0.4
1.7
1.0
0.4
1.7
1.0
0.4
1.7
1.0
0.4
1.7
1.0
0.4
pA/√ Hz
pA/√ Hz
pA/√ Hz
f
O = 1000 Hz
Input Noise
Voltage
en p-p
0.1 Hz to
10 Hz
RL ≥ 2k Ω
0.08
17
0.08
17
0.08
17
0.08
17
0.09
17
µV p-p
V/µs
Slew Rate
Gain Bandwidth
Product
SR
GBW
fO = 10 kHz
63
63
63
63
63
MHz
–6–
REV. A
Typical Performance Characteristics–OP37
10
9
100
100
90
80
70
60
50
40
30
T
V
= 25ꢁC
= ꢀ15V
A
8
741
S
7
6
5
4
I/F CORNER
LOW NOISE
10
I/F CORNER =
2.7Hz
3
2
AUDIO OP AMP
OP37
I/F CORNER
I/F CORNER = 2.7Hz
TEST TIME OF 10sec MUST BE USED
TO LIMIT LOW FREQUENCY
(<0.1Hz) GAIN.
INSTRUMENTATION AUDIO RANGE
RANGETO DC
TO 20kHz
1
1
1
10
100
1k
1
10
100
1k
0.01
0.1
1
10
100
FREQUENCY – Hz
FREQUENCY – Hz
FREQUENCY – Hz
TPC 1. Noise-Tester Frequency
Response (0.1 Hz to 10 Hz)
TPC 2. Voltage Noise Density vs.
Frequency
TPC 3. A Comparison of Op Amp
Voltage Noise Spectra
100
10
5
R1
R2
T
V
= 25ꢁC
= ꢀ15V
A
T
V
= 25ꢁC
= ꢀ15V
V
= ꢀ15V
A
S
S
S
4
3
2
1
R
– 2R1
S
AT 10Hz
AT 1kHz
1
10
0.1
AT 10Hz
AT 1kHz
RESISTOR NOISE ONLY
1
100
0.01
100
–50 –25
0
25
50
75
100 125
1k
10k
1k
10k
100k
TEMPERATURE – ꢁC
SOURCE RESISTANCE – ꢃ
BANDWIDTH – Hz
TPC 4. Input Wideband Voltage Noise
vs. Bandwidth (0.1 Hz to Frequency
Indicated)
TPC 5. Total Noise vs. Source Resistance
TPC 6. Voltage Noise Density vs.
Temperature
5
10.0
5.0
4.0
T
= 25ꢁC
A
4
3
2
1
AT 10Hz
AT 1kHz
T
= +125ꢁC
A
3.0
2.0
1.0
1.0
T
= –55ꢁC
A
T
= +25ꢁC
A
I/F CORNER = 140Hz
0.1
10
0
10
20
30
40
5
15
25
35
45
100
1k
10k
TOTAL SUPPLYVOLTAGE (V+ – V–) – Volts
TOTAL SUPPLYVOLTAGE – Volts
FREQUENCY – Hz
TPC 7. Voltage Noise Density vs.
Supply Voltage
TPC 8. Current Noise Density vs.
Frequency
TPC 9. Supply Current vs. Supply
Voltage
–7–
REV. A
OP37
6
4
60
50
40
OP37C
OP37B
T
= 25ꢁC
A
V
= ꢀ15V
S
2
10
30
20
0
OP37A
–2
–4
OP37C/G
OP37F
10
0
OP37B
OP37A
–6
6
–10
–20
–30
OP37A
OP37B
5
4
OP37A/E
2
–40
0
TRIMMINGWITH
10kꢃ POT DOES
–2
–50
–60
–70
NOT CHANGE
–4
–6
TCV
OS
OP37C
1
–75 –50 –25
0
25 50 75 100 125 150 175
0
1
2
3
4
5
0
1
2
3
4
5
6
7
TEMPERATURE – ꢁC
TIME AFTER POWER ON – MINUTES
TIME – MONTHS
TPC 10. Offset Voltage Drift of Eight
Representative Units vs. Temperature
TPC 12. Warm Up Offset Voltage Drift
TPC 11. Long-Term Offset Voltage
Drift of Six Representative Units
30
50
50
V
= +15V
S
V
= +15V
V = ꢀ15V
S
S
25
20
40
30
20
10
40
30
20
T
25ꢁC
=
T = 70ꢁC
A
A
THERMAL SHOCK
RESPONSE BAND
15
10
5
OP37C
OP37C
OP37B
10
0
DEVICE IMMERSED
IN 70ꢁC OIL BATH
OP37B
OP37A
OP37A
25
0
–20
0
0
20
40
100
60
80
–75 –50 –25
0
50 75 100 125
–50 –25
0
25 50 75 100 125 150
TEMPERATURE – ꢁC
TIME – Seconds
TEMPERATURE – ꢁC
TPC 13. Offset Voltage Change Due
to Thermal Shock
TPC 14. Input Bias Current vs. Temperature
TPC 15. Input Offset Current vs.
Temperature
80
75
70
65
60
55
30
25
90
60
50
40
30
20
10
0
–80
140
T
V
= 25ꢁC
= ꢀ15V
A
V
= ꢀ15V
T
V
R
= 25ꢁC
= ꢀ15V
2kꢃ
S
A
85
80
75
70
65
S
ꢄM
–100
–120
–140
–160
–180
–200
–220
120
100
80
60
40
20
0
S
L
PHASE
MARGIN
= 71ꢁ
GBW
60
55
A
= 5
V
50
45
40
20
15
10
SLEW
–10
100k
2
3
4
5
6
7
8
1
10
–50 –25
0
25
50
75
100 125
10
10 10
10
10 10 10
1M
10M
100M
FREQUENCY – Hz
FREQUENCY – Hz
TEMPERATURE – ꢁC
TPC 16. Open-Loop Gain vs. Frequency
TPC 17. Slew Rate, Gain Bandwidth
Product, Phase Margin vs. Temperature
TPC 18. Gain, Phase Shift vs. Frequency
–8–
REV. A
OP37
2.5
2.0
1.5
1.0
0.5
0
28
24
20
16
12
8
18
16
T
V
= 25ꢁC
= ꢀ15V
T
= 25ꢁC
A
A
S
POSITIVE
SWING
14
12
10
8
R
= 2kꢃ
L
NEGATIVE
SWING
R
= 1kꢃ
L
6
4
2
T
= 25ꢁC
4
A
0
V
= ꢀ15V
S
–2
100
0
10
0
10
20
30
40
50
4
5
6
7
10
1k
10k
10
10
TOTAL SUPPLYVOLTAGE – Volts
LOAD RESISTANCE – ꢃ
FREQUENCY – Hz
TPC 19. Open-Loop Voltage Gain vs.
Supply Voltage
TPC 20. Maximum Output Swing vs.
Frequency
TPC 21. Maximum Output Voltage
vs. Load Resistance
80
60
40
1µs
5V
200ns
20mV
+50mV
0V
+10V
0V
T
V
A
= 25ꢁC
= ꢀ15V
= +5
A
T
V
A
= 25ꢁC
= ꢀ15V
= +5 (1kꢃ, 250ꢃ)
A
–10V
S
V
V
A
= ꢀ15V
= 20mV
= +5 (1kꢃ, 250ꢃ)
20
0
S
S
–50mV
V
IN
V
(1kꢃ, 250ꢃ)
V
0
500
1000
1500
2000
CAPACITIVE LOAD – pF
TPC 22. Small-Signal Overshoot vs.
Capacitive Load
TPC 23. Large-Signal Transient
Response
TPC 24. Small-Signal Transient
Response
60
140
16
V
T
= ꢀ15V
= 25ꢁC
= ꢀ10V
T
V
= 25ꢁC
= ꢀ15V
S
A
T = –55ꢁC
A
12
8
A
S
V
T
= +25ꢁC
120
100
80
CM
A
50
40
30
20
10
T
= +125ꢁC
A
4
I
(+)
SC
0
T
= –55ꢁC
A
–4
–8
–12
–16
I
(–)
SC
T
= +25ꢁC
A
60
T
= +125ꢁC
ꢀ10
A
40
1k
0
1
2
3
4
5
0
ꢀ5
ꢀ15
ꢀ20
10k
100k
FREQUENCY – Hz
1M
10M
TIME FROM OUTPUT SHORTEDTO
SUPPLYVOLTAGE – Volts
GROUND – MINUTES
TPC 25. Short-Circuit Current vs. Time
TPC 26. CMRR vs. Frequency
TPC 27. Common-Mode Input Range
vs. Supply Voltage
–9–
REV. A
OP37
2.4
2.2
2.0
1.8
1.6
1.4
1.2
1.0
0.8
0.1ꢂF
T
V
= 25ꢁC
= ꢀ15V
A
1 SEC/DIV
S
100kꢃ
OP37
10ꢃ
D.U.T.
2kꢃ
VOLTAGE
GAIN
= 50,000
22ꢂF
4.3kꢃ
2.2ꢂF
OP12
100kꢃ
SCOPE ꢅ 1
= 1Mꢃ
4.7ꢂF
R
IN
110kꢃ
0.6
0.4
0.1ꢂF
24.3kꢃ
100
1k
10k
100k
LOAD RESISTANCE – ꢃ
TPC 28. Noise Test Circuit (0.1 Hz to
10 Hz)
TPC 29. Low-Frequency Noise
TPC 30. Open-Loop Voltage Gain vs.
Load Resistance
160
19
18
17
20
T
= 25ꢁC
A
T
V
A
V
= 25ꢁC
= ꢀ15V
= 5
T = 25ꢁC
A
A
140
RISE
FALL
A
= 5
S
VCL
V
120
100
80
60
40
20
0
15
10
5
= 20V p-p
O
NEGATIVE
SWING
POSITIVE
SWING
16
15
0
ꢀ3
1
10 100 1k 10k 100k 1M 10M 100M
100
1k
10k
100k
ꢀ6
ꢀ9
ꢀ12
ꢀ15
ꢀ18
ꢀ21
FREQUENCY – Hz
LOAD RESISTANCE – ꢃ
SUPPLYVOLTAGE – Volts
TPC 31. PSRP vs. Frequency
TPC 32. Slew Rate vs. Load
TPC 33. Slew Rate vs. Supply Voltage
–10–
REV. A
OP37
APPLICATIONS INFORMATION
Noise Measurements
OP37 Series units may be inserted directly into 725 and OP07
sockets with or without removal of external compensation or
nulling components. Additionally, the OP37 may be fitted to
unnulled 741type sockets; however, if conventional 741 nulling
circuitry is in use, it should be modified or removed to ensure
correct OP37 operation. OP37 offset voltage may be nulled to
zero (or other desired setting) using a potentiometer (see offset
nulling circuit).
To measure the 80 nV peak-to-peak noise specification of the
OP37 in the 0.1 Hz to 10 Hz range, the following precautions
must be observed:
• The device has to be warmed-up forat least five minutes. As
shown in the warm-up drift curve, the offset voltage typically
changes 4 µV due to increasing chip temperature after power up.
In the ten second measurement interval, these temperature-
induced effects can exceed tens of nanovolts.
The OP37 provides stable operation with load capacitances of
up to 1000 pF and 10 V swings; larger capacitances should be
decoupled with a 50 Ω resistor inside the feedback loop. Closed
loop gain must be at least five. For closed loop gain between five
to ten, the designer should consider both the OP27 and the OP37.
For gains above ten, the OP37 has a clear advantage over the
unity stable OP27.
• For similar reasons, the device has to be well-shielded from
air currents. Shielding minimizes thermocouple effects.
• Sudden motion in the vicinity of the device can also
“feedthrough” to increase the observed noise.
• The test time to measure 0.1 Hz to l0 Hz noise should not
exceed 10 seconds. As shown in the noise-tester frequency
response curve, the 0.1 Hz corner is defined by only one zero.
The test time of ten seconds acts as an additional zero to eliminate
noise contributions from the frequency band below 0.1 Hz.
Thermoelectric voltages generated by dissimilar metals at the input
terminal contacts can degrade the drift performance. Best
operation will be obtained when both input contacts are main-
tained at the same temperature.
• A noise-voltage-density test is recommended when measuring
noise on a large number of units. A 10 Hz noise-voltage-density
measurement will correlate well with a 0.1 Hz-to-10 Hz peak-to-peak
noise reading, since both results are determined by the white
noise and the location of the 1/f corner frequency.
10kꢃ R
P
V+
–
OP37
OUTPUT
Optimizing Linearity
+
Best linearity will be obtained by designing for the minimum
output current required for the application. High gain and
excellent linearity can be achieved by operating the op amp with
a peak output current of less than 10 mA.
V–
Figure 1. Offset Nulling Circuit
Offset Voltage Adjustment
Instrumentation Amplifier
A three-op-amp instrumentation amplifier provides high gain and
wide bandwidth. The input noise of the circuit below is 4.9 nV/√Hz.
The gain of the input stage is set at 25 and the gain of the second
stage is 40; overall gain is 1000. The amplifier bandwidth of
800 kHz is extraordinarily good for a precision instrumentation
amplifier. Set to a gain of 1000, this yields a gain bandwidth
product of 800 MHz. The full-power bandwidth for a 20 V p-p
output is 250 kHz. Potentiometer R7 provides quadrature
trimming to optimize the instrumentation amplifier’s ac common-
mode rejection.
The input offset voltage of the OP37 is trimmed at wafer level.
However, if further adjustment of VOS is necessary, a 10 kΩ trim
potentiometer may be used. TCVOS is not degraded (see offset
nulling circuit). Other potentiometer values from 1 kΩ to 1 MΩ
can be used with a slight degradation (0.1 µV/°C to 0.2 µV/°C) of
TCVOS. Trimming to a value other than zero creates a drift of
approximately (VOS/300) µV/°C. For example, the change in TCVOS
will be 0.33 µV/°C if VOS is adjusted to 100 µV. The offset voltage
adjustment range with a 10 kΩ potentiometer is 4 mV. If smaller
adjustment range is required, the nulling sensitivity can be reduced
by using a smaller pot in conjunction with fixed resistors. For
example, the network below will have a 280 µV adjustment range.
R5
500ꢃ
0.1%
R8
20kꢃ
0.1%
+
INPUT (–)
OP37
–
R1
4.7kꢃ
1kꢃ POT
4.7kꢃ
8
1
5kꢃ
0.1%
R3
V+
–
390ꢃ
R7
V
OUT
R4
5kꢃ
0.1%
100kꢃ OP37
C1
100pF
R2
100ꢃ
Figure 2. TBD
+
+18V
R6
R9
19.8kꢃ
500ꢃ
0.1%
–
OP37
R10
500ꢃ
INPUT (+)
+
NOTES:
TRIM R2 FOR A
OP37
= 1000
VCL
TRIM R10 FOR dc CMRR
TRIM R7 FOR MINIMUMV
AT V
= 20V p-p, 10kHz
CM
OUT
Figure 4a. TBD
–18V
Figure 3. Burn-In Circuit
REV. A
–11–
OP37
140
1k
T
= 25ꢁC
A
OP08/108
5534
V
= ꢀ15V
= 20V p-p
S
R
= 0
S
500
V
CM
120
100
80
ACTRIM @ 10kHz
= 0
R
S
OP07
1
R
= 1kꢃ
S
BALANCED
2
100
50
OP27/37
R
= 100ꢃ,
1kꢃ UNBALANCED
S
1 R UNMATCHED
S
e.g.R = R = 10kꢃ, R = 0
S
S1
S2
2 R MATCHED
S
e.g.R = 10kꢃ, R = R = 5kꢃ
S
S1
S2
60
R
S1
R
S2
REGISTER
NOISE ONLY
40
10
50
10
100
1k
10k
100k
1M
100
500
1k
5k
10k
50k
FREQUENCY – Hz
R
– SOURCE RESISTANCE – ꢃ
S
Figure 4b. TBD
Figure 6. Peak-to-Peak Noise (0.1 Hz to 10 Hz) vs. Source
Resistance (Includes Resistor Noise)
Comments on Noise
The OP37 is a very low-noise monolithic op amp. The outstanding
input voltage noise characteristics of the OP37 are achieved
mainly by operating the input stage at a high quiescent current.
The input bias and offset currents, which would normally increase,
are held to reasonable values by the input bias current cancellation
circuit. The OP37A/E has IB and IOS of only 40 nA and 35 nA
respectively at 25°C. This is particularly important when the input
has a high source resistance. In addition, many audio amplifier
designers prefer to use direct coupling. The high IB. TCVOS of
previous designs have made direct coupling difficult, if not
impossible, to use.
At RS < 1 kΩ key the OP37’s low voltage noise is maintained.
With RS < 1 kΩ, total noise increases, but is dominated by the
resistor noise rather than current or voltage noise. It is only
beyond Rs of 20kil that current noise starts to dominate. The
argument can be made that current noise is not important for
applications with low to-moderate source resistances. The
crossover between the OP37 and OP07 and OP08 noise occurs
in the 15 kΩ to 40 kΩ region.
100
50
1
2
100
OP08/108
50
1
OP07
10
OP08/108
5534
1 R UNMATCHED
S
2
5
e.g.R = R = 10kꢃ, R = 0
S
S1 S2
OP07
10
2 R MATCHED
S
OP27/37
e.g.R = 10kꢃ, R = R = 5kꢃ
S1 S2
S
R
S1
1 R UNMATCHED
S
5
5534
R
S2
e.g.R = R = 10kꢃ, R = 0
REGISTER
S
S1
S2
2 R MATCHED
NOISE ONLY
S
1
50
e.g.R = 10kꢃ, R = R = 5kꢃ
S1 S2
S
OP27/37
100
500
1k
5k
10k
50k
R
S1
R
– SOURCE RESISTANCE – ꢃ
S
R
S2
REGISTER
NOISE ONLY
Figure 7. !0 Hz Noise vs. Source resistance (Inlcludes
Resistor Noise)
1
50
100
500
1k
5k
10k
50k
R
– SOURCE RESISTANCE – ꢃ
S
Figure 6 shows the 0.1 Hz to 10 Hz peak-to-peak noise. Here
the picture is less favorable; resistor noise is negligible, current
noise becomes important because it is inversely proportional to
the square-root of frequency. The crossover with the OP-07
occurs in the 3 kΩ to 5 kΩ range depending on whether bal-
anced or unbalanced source resistors are used (at 3 kΩ the IB.
IOS error also can be three times the VOS spec.).
Figure 5. Noise vs. Resistance (Including Resistor Noise
@ 1000 Hz)
Voltage noise is inversely proportional to the square-root of bias
current, but current noise is proportional to the square-root of
bias current. The OP37’s noise advantage disappears when high
source-resistors are used. Figures 5, 6, and 7 compare OP-37
observed total noise with the noise performance of other devices
in different circuit applications.
Therefore, for low-frequency applications, the OP07 is better
than the OP27/37 when Rs > 3 kΩ. The only exception is when
gain error is important. Figure 3 illustrates the 10 Hz noise. As
expected, the results are between the previous two figures.
Total noise = [( Voltage noise)2 + (current noise ϫ RS)2 +
(resistor noise_]1/2
For reference, typical source resistances of some signal sources
are listed in Table I.
Figure 5 shows noise versus source resistance at 1000 Hz. The
same plot applies to wideband noise. To use this plot, just multiply
the vertical scale by the square-root of the bandwidth.
–12–
REV. A
OP37
Table I. TBD
Source
by only 0.7 dB. With a 1 kΩ source, the circuit noise measures
63 dB below a 1 mV reference level, unweighted, in a 20 kHz
noise bandwidth.
Device
Impedance Comments
Gain (G) of the circuit at 1 kHz can be calculated by the expression:
Straln Gauge
<500 Ω
Typically used in low-frequency
applications.
R
G = 0.101 1+
1
Magnetic
Tapehead
<1500 Ω
Low IB very important to reduce
set-magnetization problems when
direct coupling is used. OP37
IB can be neglected.
R
3
For the values shown, the gain is just under 100 (or 40 dB).
Lower gains can be accommodated by increasing R3, but gains
higher than 40 dB will show more equalization errors because of
the 8 MHz gain bandwidth of the OP27.
Magnetic
Phonograph
Cartridges
<1500 Ω
Similar need for low IB in direct
coupled applications. OP47 will not
introduce any self-magnetization
problem.
This circuit is capable of very low distortion over its entire range,
generally below 0.01% at levels up to 7 V rms. At 3 V output
levels, it will produce less than 0.03% total harmonic distortion
at frequencies up to 20 kHz.
Linear Variable <1500 Ω
Differential
Used in rugged servo-feedback
applications. Bandwidth of interest
is 400 Hz to 5 kHz.
Transformer
Capacitor C3 and resistor R4form a simple –6 dB per octave
rumble filter, with a corner at 22 Hz. As an option, the switch
selected shunt capacitor C4, a nonpolarized electrolytic, bypasses
the low-frequency rolloff. Placing the rumble filter’s high-pass
action after the preamp has the desirable result of discriminating
against the RIAA amplified low frequency noise components
and pickup-produced low-frequency disturbances.
Audio Applications
The following applications information has been abstracted from
a PMI article in the 12/20/80 issue of Electronic Design magazine
and updated.
C4 (2)
R5
220ꢂF
100kꢃ
+
+
A preamplifier for NAB tape playback is similar to an RIAA
phono preamp, though more gain is typically demanded, along
with equalization requiring a heavy low-frequency boost. The
circuit In Figure 4 can be readily modified for tape use, as
shown by Figure 5.
MOVING MAGNET
CARTRIDGE INPUT
LF ROLLOFF
OUT
C3
0.47ꢂF
IN
A1
OP27
Ca
150pF
Ra
R4
75kꢃ
C1
0.03ꢂF
47.5kꢃ
OUTPUT
R1
97.6kꢃ
–
0.47ꢂF
R2
7.87kꢃ
C2
0.01ꢂF
OP37
TAPE
HEAD
Ra
Ca
+
15kꢃ
R3
100ꢃ
R1
33kꢃ
R2
5kꢃ
G = 1kHz GAIN
0.01ꢂF
R1
R3
1 +
= 0.101 (
)
= 98.677 (39.9dB) AS SHOWN
100kꢃ
T1 = 3180ꢂs
T2 = 50ꢂs
Figure 8. TBD
Figure 9. TBD
Figure 8 is an example of a phono pre-amplifier circuit using the
OP27 for A1; R1-R2-C1-C2 form a very accurate RIAA net-
work with standard component values. The popular method to
accomplish RIAA phono equalization is to employ frequency-
dependent feedback around a high-quality gain block. Properly
chosen, an RC network can provide the three necessary time
constants of 3180 µs, 318 µs, and 75 µs.1
While the tape-equalization requirement has a flat high frequency
gain above 3 kHz (t2 = 50 µs), the amplifier need not be stabilized
for unity gain. The decompensated OP37 provides a greater
bandwidth and slew rate. For many applications, the idealized
time constants shown may require trimming of RA and R2 to
optimize frequency response for non ideal tape head perfor-
mance and other factors.5
For initial equalization accuracy and stability, precision metal-
film resistors and film capacitors of polystyrene or polypropylene
are recommended since they have low voltage coefficients,
dissipation factors, and dielectric absorption.4 (High-K ceramic
capacitors should be avoided here, though low-K ceramics—
such as NPO types, which have excellent dissipation factors,
and somewhat lower dielectric absorption—can be considered
for small values or where space is at a premium.)
The network values of the configuration yield a 50 dB gain at 1 kHz,
and the dc gain is greater than 70 dB. Thus, the worst-case out-
put offset is just over 500 mV. A single 0.47 µF output capacitor
can block this level without affecting the dynamic range.
The tape head can be coupled directly to the amplifier input,
since the worst-case bias current of 85 nA with a 400 mH, 100 µin.
head (such as the PRB2H7K) will not be troublesome.
The OP27 brings a 3.2 nV/√Hz voltage noise and 0.45 pA/√Hz
current noise to this circuit. To minimize noise from other sources,
R3 is set to a value of 100 Ω, which generates a voltage noise of
1.3 nV/√Hz. The noise increases the 3.2 nV/√Hz of the amplifier
One potential tape-head problem is presented by amplifier bias-
current transients which can magnetize a head. The OP27 and
REV. A
–13–
OP37
OP37 are free of bias-current transients upon power up or power
down. However, it is always advantageous to control the speed
of power supply rise and fall, to eliminate transients.
offset of this circuit will be very low, 1.7 mV or less, for a 40 dB
gain. The typical output blocking capacitor can be eliminated in
such cases, but is desirable for higher gains to eliminate switching
transients.
In addition, the dc resistance of the head should be carefully
controlled, and preferably below 1 kΩ. For this configuration,
the bias-current induced offset voltage can be greater than the
170 pV maximum offset if the head resistance is not sufficiently
controlled.
C2
1800pF
R1
121ꢃ
R2
1100ꢃ
A simple, but effective, fixed-gain transformerless microphone
preamp (Figure 10) amplifies differential signals from low imped-
ance microphones by 50 dB, and has an input impedance of 2 kΩ.
Because of the high working gain of the circuit, an OP37 helps
to preserve bandwidth, which will be 110 kHz. As the OP37 is a
decompensated device (minimum stable gain of 5), a dummy
resistor, RP, may be necessary, if the microphone is to be
unplugged. Otherwise the 100% feedback from the open input
may cause the amplifier to oscillate.
A1
OUTPUT
T1*
OP27
150ꢃ
SOURCE
R3
100ꢃ
*T1 – JENSEN JE – 115K – E
JENSENTRANSFORMERS
10735 BURBANK BLVD.
N. HOLLYWOOD, CA 91601
Figure 11. TBD
C1
5ꢂF
R1
1kꢃ
R3
R6
Capacitor C2 and resistor R2 form a 2 µs time constant in this
circuit, as recommended for optimum transient response by
the transformer manufacturer. With C2 in use, A1 must have
unity-gain stability. For situations where the 2 µs time con-
stant is not necessary, C2 can be deleted, allowing the faster
OP37 to be employed.
316kꢃ
100ꢃ
–
LOW IMPEDANCE
MICROPHONE INPUT
(Z = 50ꢃTO 200ꢃ)
Rp
30kꢃ
R7
10kꢃ
OP37
OUTPUT
+
R2
R4
R3 R4
=
Some comment on noise is appropriate to understand the
capability of this circuit. A 150 Ω resistor and R1 and R2 gain
resistors connected to a noiseless amplifier will generate 220 nV
of noise in a 20 kHz bandwidth, or 73 dB below a 1 mV reference
level. Any practical amplifier can only approach this noise level;
it can never exceed it. With the OP27 and T1 specified, the
additional noise degradation will be close to 3.6 dB (or –69.5
referenced to 1 mV).
1kꢃ
316kꢃ
R1 R2
Figure 10. TBD
Common-mode input-noise rejection will depend upon the match
of the bridge-resistor ratios. Either close-tolerance (0.1%) types
should be used, or R4 should be trimmed for best CMRR. All
resistors should be metal-film types for best stability and low noise.
References
Noise performance of this circuit is limited more by the input
resistors R1 and R2 than by the op amp, as R1 and R2 each
generate a 4 nV√Hz noise, while the op amp generates a 3.2 nV√Hz
noise. The rms sum of these predominant noise sources will be
about 6 nV√Hz, equivalent to 0.9 µV in a 20 kHz noise bandwidth,
or nearly 61 dB below a l mV input signal. Measurements confirm
this predicted performance.
1. Lipshitz, S.P, “On RIAA Equalization Networks,” JAES, Vol. 27, June 1979,
p. 458-4S1.
2. Jung, W.G., IC Op Amp Cookbook, 2nd Ed., H.W. Sams and Company,
1980.
3. Jung, W.G., Audio /C Op Amp Applications, 2nd Ed., H.W. Sams and Com-
pany, 1978.
4. Jung, W.G., and Marsh, R.M., “Picking Capacitors.” Audio, February &
March, 1980.
5. Otala, M., “Feedback-Generated Phase Nonlinearity in Audio Amplifiers,”
London AES Convention, March 1980, preprint 197B.
6. Stout, D.F., and Kaufman, M., Handbook of Operational Amplifier Circuit
Design, New York, McGraw Hill, 1976.
For applications demanding appreciably lower noise, a high quality
microphone-transformer-coupled preamp (Figure 11) incorporates
the internally compensated. T1 is a JE-115K-E 150 Ω/15 kΩ
transformer which provides an optimum source resistance for
the OP27 device. The circuit has an overall gain of 40 dB, the
product of the transformer’s voltage setup and the op amp’s
voltage gain.
Gain may be trimmed to other levels, if desired, by adjusting R2
or R1. Because of the low offset voltage of the OP27, the output
–14–
REV. A
OP37
OUTLINE DIMENSIONS
Dimensions shown in inches and (mm).
8-Lead Hermetic DIP
(Z Suffix)
0.005 (0.13) 0.055 (1.4)
MIN
MAX
8
5
0.310 (7.87)
0.220 (5.59)
PIN 1
1
4
0.100 (2.54) BSC
0.405 (10.29) MAX
0.320 (8.13)
0.290 (7.37)
0.060 (1.52)
0.015 (0.38)
0.200 (5.08)
MAX
0.150
(3.81)
MIN
0.200 (5.08)
0.125 (3.18)
0.015 (0.38)
0.008 (0.20)
SEATING
PLANE
15°
0°
0.023 (0.58) 0.070 (1.78)
0.014 (0.36) 0.030 (0.76)
Epoxy Mini-Dip
(P Suffix)
0.430 (10.92)
0.348 (8.84)
8
5
0.280 (7.11)
0.240 (6.10)
1
4
0.325 (8.25)
0.300 (7.62)
PIN 1
0.100 (2.54)
BSC
0.060 (1.52)
0.015 (0.38)
0.210
(5.33)
MAX
0.195 (4.95)
0.115 (2.93)
0.130
(3.30)
MIN
0.160 (4.06)
0.115 (2.93)
0.015 (0.381)
0.008 (0.204)
0.022 (0.558) 0.070 (1.77) SEATING
0.014 (0.356) 0.045 (1.15)
PLANE
8-Lead SO
(S Suffix)
0.1968 (5.00)
0.1890 (4.80)
8
1
5
4
0.2440 (6.20)
0.2284 (5.80)
0.1574 (4.00)
0.1497 (3.80)
PIN 1
0.0196 (0.50)
0.0099 (0.25)
0.0500 (1.27)
BSC
ꢅ 45ꢁ
0.0688 (1.75)
0.0532 (1.35)
0.0098 (0.25)
0.0040 (0.10)
SEATING
PLANE
8ꢁ
0ꢁ
0.0500 (1.27)
0.0160 (0.41)
0.0192 (0.49)
0.0138 (0.35)
0.0098 (0.25)
0.0075 (0.19)
REV. A
–15–
OP37
Revision History
Location
Page
Data Sheet changed from REV. B to REV. C.
Edits to FEATURES . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1
Edits to ORDERING INFORMATION . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1
Edits to PIN CONNECTIONS . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1
Edits to ABSOLUTE MAXIMUM RATINGS . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 2
Edits to PACKAGE TYPE . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 2
Edits to ELECTRICAL CHARACTERISTICS . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 3
Edits to APPLICATIONS INFORMATION . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 8
–16–
REV. A
相关型号：
OP37FJ
IC OP-AMP, 140 uV OFFSET-MAX, 63 MHz BAND WIDTH, MBCY8, TO-99, 8 PIN, Operational Amplifier
ADI
OP37FZ
Operational Amplifier, 1 Func, 60uV Offset-Max, BIPolar, CDIP8, HERMETIC SEALED, CERDIP-8
ROCHESTER
OP37FZ
IC OP-AMP, 60 uV OFFSET-MAX, 63 MHz BAND WIDTH, CDIP8, HERMETIC SEALED, CERDIP-8, Operational Amplifier
ADI
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