AD8099ARD-REEL7
更新时间：2024-09-18 02:07:23
品牌：ADI
描述：Ultralow Distortion, High Speed 0.95 nV/Hz Voltage Noise Op Amp
概述
数据手册
替代型号AD8099ARD-REEL7 概述
Ultralow Distortion, High Speed 0.95 nV/Hz Voltage Noise Op Amp 超低失真，高速0.95内华达州/ Hz的电压噪声运算放大器 放大器、缓冲器
AD8099ARD-REEL7 数据手册
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PDF下载Ultralow Distortion, High Speed
0.95 nV/
√
Hz Voltage Noise Op Amp
AD8099
FEATURES
Ultralow noise: 0.95 nV/√Hz, 2.6 pA/√Hz
APPLICATIONS
Pre-amplifiers
Receivers
Ultralow distortion
2nd harmonic RL = 1 kΩ , G = +2
−92 dB @ 10 MHz
3rd harmonic RL = 1 kΩ , G = +2
−105 dB @ 10 MHz
Instrumentation
Filters
IF and baseband amplifiers
A-to-D drivers
DAC buffers
High speed
Optical electronics
GBWP: 3.8 GHz
–3 dB bandwidth:
700 MHz (G = +2)
550 MHz (G = +10)
CONNECTION DIAGRAMS
Slew rate:
475 V/µs (G = +2)
1350 V/µs (G = +10)
New pinout
Custom external compensation, gain range –1, +2 to +10
Supply current: 15 mA
Offset voltage: 0.5 mV max
Wide supply voltage range: 5 V to 12 V
1
2
3
4
8
7
6
5
1
2
3
4
8
7
6
5
DISABLE
FEEDBACK
–IN
+V
V
FEEDBACK
–IN
DISABLE
S
+V
S
OUT
C
+IN
V
OUT
C
+IN
–V
–V
C
C
S
S
Figure 1. 8-Lead CSP (CP-8)
Figure 2. 8-Lead SOIC-ED (RD-8)
GENERAL DESCRIPTION
The AD8099 is an ultralow noise (0.95 nV/√ ) and distortion
Hz
The AD8099 is available in a 3 mm × 3 mm lead frame chip
scale package (LFCSP) with a new pinout that is specifically
optimized for high performance, high speed amplifiers. The
new LFCSP package and pinout enable the breakthrough
performance that previously was not achievable with amplifiers.
The AD8099 is rated to work over the extended industrial
temperature range, −40°C to +125°C.
(–92 dBc @10 MHz) voltage feedback op amp, the combination
of which make it ideal for 16- and 18-bit systems. The AD8099
features a new, highly linear, low noise input stage that increases
the full power bandwidth (FPBW) at low gains with high slew
rates. ADI’s proprietary next generation XFCB process enables
such high performance amplifiers with relatively low power.
–40
G = +2
The AD8099 features external compensation, which lets the
user set the gain bandwidth product. External compensation
allows gains from +2 to +10 with minimal trade-off in band-
width. The AD8099 also features an extremely high slew rate of
1350 V/µs, giving the designer flexibility to use the entire
dynamic range without trading off bandwidth or distortion.
The AD8099 settles to 0.1% in 18 ns and recovers from
overdrive in 50 ns.
V
V
= 2V p-p
OUT
= ±5V
–50
–60
S
R
= 1kΩ
L
–70
–80
–90
–100
–110
–120
–130
The AD8099 drives 100 Ω loads at breakthrough performance
levels with only 15 mA of supply current. With the wide supply
voltage range (5 V to 12 V), low offset voltage (0.1 mV typ),
wide bandwidth (700 MHz for G = +2), and a GBWP up to
3.8 GHz, the AD8099 is designed to work in a wide variety of
applications.
SOLID LINE – SECOND HARMONIC
DOTTED LINE – THIRD HARMONIC
0.1
1.0
FREQUENCY (MHz)
10.0
Figure 3 . Harmonic Distortion vs. Frequency and Gain (SOIC)
Rev. B
Information furnished by Analog Devices is believed to be accurate and reliable.
However, no responsibility is assumed by Analog Devices for its use, nor for any
infringements of patents or other rights of third parties that may result from its use.
Specifications subject to change without notice. No license is granted by implication
or otherwise under any patent or patent rights of Analog Devices. Trademarks and
registered trademarks are the property of their respective owners.
One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A.
Tel: 781.329.4700
Fax: 781.326.8703
www.analog.com
© 2004 Analog Devices, Inc. All rights reserved.
AD8099
TABLE OF CONTENTS
Specifications..................................................................................... 3
Specifications with 5 V Supply................................................. 3
Specifications with +5 V Supply................................................. 4
Absolute Maximum Ratings............................................................ 5
Maximum Power Dissipation ..................................................... 5
ESD Caution.................................................................................. 5
Typical Performance Characteristics ............................................. 6
Theory of Operation ...................................................................... 15
Applications..................................................................................... 16
Using the AD8099 ...................................................................... 16
Circuit Components................................................................... 16
Recommended Values ............................................................... 17
Circuit Configurations .............................................................. 17
Performance vs. Component values ........................................ 19
Total Output Noise Calculations and Design......................... 20
Input Bias Current and DC Offset........................................... 21
Pin and Input Bias Cancellation............................. 21
DISABLE
16-Bit ADC Driver..................................................................... 22
Circuit Considerations .............................................................. 23
Design Tools and Technical Support....................................... 23
Outline Dimensions....................................................................... 25
Ordering Guide............................................................................... 26
REVISION HISTORY
6/04—Data Sheet changed from REV. A to REV. B
Change to General Description...................................................... 1
Changes to Maximum Power Dissipation section ...................... 5
Changes to Applications section .................................................. 16
Changes to Table 7.......................................................................... 24
Changes to Ordering Guide .......................................................... 26
1/04—Data Sheet changed from REV. 0 to REV. A
Inserted new Figure 3................................................................... 1
Changes to Specifications............................................................ 3
Inserted new Figures 22 to 34 ..................................................... 8
Inserted new Figures 51 to 55 ................................................... 14
Changes to Theory of Operation section ................................ 16
Changes to Circuit Components section................................. 17
Changes to Table 4...................................................................... 18
Changes to Figure 60.................................................................. 18
Changes to Total Output Noise Calculations and
Design section........................................................................ 21
Changes to Figure 60.................................................................. 22
Changes to Figure 62.................................................................. 23
Changes to 16-Bit ADC Driver section................................... 23
Changes to Table 6...................................................................... 23
Additions to PCB Layout section ............................................. 23
11/03—Revision 0: Initial Version
Rev. B | Page 2 of 28
AD8099
SPECIFICATIONS
SPECIFICATIONS WITH 5 V SUPPLY
TA = 25°C, G = +2, RL = 1 kΩ to ground, unless otherwise noted. Refer to Figure 60 through Figure 66 for component values and
gain configurations .
Table 1.
Parameter
Conditions
Min
Typ
Max Unit
DYNAMIC PERFORMANCE
–3 dB Bandwidth
G = +5, VOUT = 0.2 V p-p
G = +5, VOUT = 2 V p-p
G = +2, VOUT = 0.2 V p-p
G = +10, VOUT = 6 V Step
G = +2, VOUT = 2 V Step
G = +2, VOUT = 2 V Step
450
205
510
235
34/25
1350
470
MHz
MHz
MHz
V/µs
V/µs
ns
Bandwidth for 0.1 dB Flatness (SOIC/CSP)
Slew Rate
1120
435
Settling Time to 0.1%
18
NOISE/DISTORTION PERFORMANCE
Harmonic Distortion (dBc) HD2/HD3
fC = 500 kHz, VOUT = 2 V p-p, G = +10
fC = 10 MHz, VOUT = 2 V p-p, G = +10
f = 100 kHz
–102/–111
–84/–92
0.95
dBc
dBc
Input Voltage Noise
Input Current Noise
Hz
nV/√
pA/√
pA/√
DISABLE
DISABLE
2.6
Hz
Hz
f = 100 kHz,
f = 100 kHz,
pin floating
pin = +VS
5.2
DC PERFORMANCE
Input Offset Voltage
Input Offset Voltage Drift
Input Bias Current
0.1
2.3
–6
0.5
mV
µV/°C
µA
DISABLE
DISABLE
–13
–2
pin floating
pin = +VS
–0.1
3
0.06
85
µA
Input Bias Current Drift
Input Bias Offset Current
Open-Loop Gain
nA/°C
µA
dB
1
82
98
INPUT CHARACTERISTICS
Input Resistance
Differential mode
Common mode
4
10
2
kΩ
MΩ
pF
V
Input Capacitance
Input Common-Mode Voltage Range
Common-Mode Rejection Ratio
–3.7 to +3.7
105
VCM
=
2.5 V
dB
DISABLE
PIN
DISABLE
Output disabled
DISABLE
<2.4
105
V
Input Voltage
Turn-Off Time
ns
50% of
VIN = 0.5 V, G = +2
DISABLE
to < 10% of final VOUT
,
Turn-On Time
39
ns
50% of
to < 10% of final VOUT
,
VIN = 0.5 V, G = +2
Enable Pin Leakage Current
DISABLE
DISABLE
17
35
21
44
µA
µA
=+5 V
= –5 V
DISABLE
Pin Leakage Current
OUTPUT CHARACTERISTICS
Output Overdrive Recovery Time (Rise/Fall)
Output Voltage Swing
VIN = -2.5 V to 2.5 V, G =+2
RL = 100 Ω
RL = 1 kΩ
30/50
–3.6 to +3.7
–3.8 to +3.8
131/178
–61
ns
V
V
mA
dB
–3.4 to +3.5
–3.7 to +3.7
Short-Circuit Current
Off Isolation
Sinking and sourcing
DISABLE
f = 1 MHz,
= low
POWER SUPPLY
Operating Range
Quiescent Current
5
15
1.7
91
94
6
16
2
V
mA
mA
dB
dB
Quiescent Current (Disabled)
Positive Power Supply Rejection Ratio
Negative Power Supply Rejection Ratio
DISABLE
= Low
+VS = 4 V to 6 V, –VS = –5 V (input referred)
+VS = 5 V, –VS = –6 V to –4 V (input referred)
85
86
Rev. B | Page 3 of 28
AD8099
SPECIFICATIONS WITH +5 V SUPPLY
VS = 5 V @ TA = 25°C, G = +2, RL = 1 kΩ to midsupply, unless otherwise noted. Refer to Figure 60 through Figure 66 for component
values and gain configurations .
Table 2.
Parameter
Conditions
Min
Typ
Max
Unit
DYNAMIC PERFORMANCE
–3 dB Bandwidth
G = +5, VOUT = 0.2 V p-p
G = +5, VOUT = 2 V p-p
G = +2, VOUT = 0.2 V p-p
G = +10, VOUT = 2 V Step
G = +2, VOUT = 2 V Step
G = +2, VOUT = 2 V Step
415
165
440
210
33/23
715
365
18
MHz
MHz
MHz
V/µs
V/µs
ns
Bandwidth for 0.1 dB Flatness (SOIC/CSP)
Slew Rate
630
340
Settling Time to 0.1%
NOISE/DISTORTION PERFORMANCE
Harmonic Distortion (dBc) HD2/HD3
fC = 500 kHz, VOUT = 1 V p-p, G = +10
fC = 10 MHz, VOUT = 1 V p-p, G = +10
f = 100 kHz
–82/–94
–80/–75
0.95
dBc
dBc
Input Voltage Noise
Input Current Noise
Hz
nV/√
pA/√
pA/√
DISABLE
DISABLE
2.6
Hz
Hz
f = 100 kHz,
f = 100 kHz,
pin floating
pin = +VS
5.2
DC PERFORMANCE
Input Offset Voltage
Input Offset Voltage Drift
Input Bias Current
0.1
2.5
–6.2
–0.2
0.05
2.4
0.5
mV
µV/°C
µA
DISABLE
DISABLE
–13
–2
1
pin floating
pin = +VS
µA
Input Bias Offset Current
Input Bias Offset Current Drift
Open-Loop Gain
µA
nA/°C
dB
VOUT = 1 V to 4 V
76
88
81
INPUT CHARACTERISTICS
Input Resistance
Differential mode
Common mode
4
10
2
kΩ
MΩ
pF
V
Input Capacitance
Input Common-Mode Voltage Range
Common-Mode Rejection Ratio
1.3 to 3.7
105
VCM = 2 V to 3 V
Output disabled
dB
DISABLE
PIN
DISABLE
<2.4
105
V
Input Voltage
Turn-Off Time
DISABLE
ns
50% of
VIN = 0.5 V, G = +2
DISABLE
to <10% of Final VOUT
,
Turn-On Time
61
ns
50% of
to <10% of Final VOUT
,
VIN = 0.5 V, G = +2
Enable Pin Leakage Current
DISABLE
DISABLE
16
33
21
44
µA
µA
= 5 V
= 0 V
DISABLE
Pin Leakage Current
OUTPUT CHARACTERISTICS
Overdrive Recovery Time (Rise/Fall)
Output Voltage Swing
VIN = 0 to 2.5 V, G = +2
RL = 100 Ω
RL = 1 kΩ
50/70
1.2 to 3.8
1.2 to 3.8
60/80
ns
V
V
mA
dB
1.5 to 3.5
1.2 to 3.8
Short-Circuit Current
Off Isolation
Sinking and Sourcing
DISABLE
–61
f = 1 MHz,
= Low
POWER SUPPLY
Operating Range
Quiescent Current
5
14.5
1.4
89
6
15.4
1.7
V
mA
mA
dB
dB
Quiescent Current (Disabled)
Positive Power Supply Rejection Ratio
Negative Power Supply Rejection Ratio
DISABLE
= Low
+VS = 4.5 V to 5.5 V, –VS = 0 V (input referred)
+VS =5 V, -VS= –0.5 V to +0.5 V (input referred)
84
84
90
Rev. B | Page 4 of 28
AD8099
ABSOLUTE MAXIMUM RATINGS
Table 3.
Parameter
The difference between the total drive power and the load
power is the drive power dissipated in the package.
Rating
Supply Voltage
12.6 V
PD = Quiescent Power + (Total Drive Power – Load Power)
Power Dissipation
See Figure 4
1.8 V
10mA
–65°C to +125°C
–40°C to +125°C
300°C
Differential Input Voltage
Differential Input Current
Storage Temperature
Operating Temperature Range
Lead Temperature Range (Soldering 10 sec)
Junction Temperature
2
⎛
⎜
⎜
⎝
⎞
⎟
⎟
⎠
VS VOUT
VOUT
RL
PD =
(
VS × IS
)
+
×
–
2
RL
RMS output voltages should be considered. If RL is referenced to
VS–, as in single-supply operation, then the total drive power is
VS × IOUT. If the rms signal levels are indeterminate, consider the
worst case, when VOUT = VS/4 for RL to midsupply:
150°C
Stresses above those listed under Absolute Maximum Ratings
may cause permanent damage to the device. This is a stress
rating only; functional operation of the device at these or any
other conditions above those indicated in the operational
section of this specification is not implied. Exposure to absolute
maximum rating conditions for extended periods may affect
device reliability.
2
VS /4
RL
)
PD =
(
VS ×IS +
)
In single-supply operation with RL referenced to VS–, worst case
is VOUT = VS/2.
Airflow will increase heat dissipation, effectively reducing θJA.
Also, more metal directly in contact with the package leads
from metal traces, through holes, ground, and power planes will
reduce the θJA. Soldering the exposed paddle to the ground
plane significantly reduces the overall thermal resistance of the
package. Care must be taken to minimize parasitic capaci-
tances at the input leads of high speed op amps, as discussed in
the PCB Layout section.
MAXIMUM POWER DISSIPATION
The maximum safe power dissipation in the AD8099 package is
limited by the associated rise in junction temperature (TJ) on
the die. The plastic encapsulating the die will locally reach the
junction temperature. At approximately 150°C, which is the
glass transition temperature, the plastic will change its
properties. Even temporarily exceeding this temperature limit
may change the stresses that the package exerts on the die,
permanently shifting the parametric performance of the
AD8099. Exceeding a junction temperature of 150°C for an
extended period can result in changes in silicon devices,
potentially causing failure.
Figure 4 shows the maximum safe power dissipation in the
package versus the ambient temperature for the exposed paddle
(e-pad) SOIC-8 (70°C/W), and CSP (70°C/W), packages on a
JEDEC standard 4-layer board. θJA values are approximations.
The still-air thermal properties of the package and PCB (θJA),
the ambient temperature (TA), and the total power dissipated in
the package (PD) determine the junction temperature of the die.
The junction temperature can be calculated as
4.0
3.5
3.0
2.5
2.0
TJ = TA +
PD × θJA
The power dissipated in the package (PD) is the sum of the
quiescent power dissipation and the power dissipated in the
package due to the load drive for all outputs. The quiescent
power is the voltage between the supply pins (VS) times the
quiescent current (IS). Assuming the load (RL) is referenced to
midsupply, the total drive power is VS/2 × IOUT, some of which is
dissipated in the package and some in the load (VOUT × IOUT).
1.5
LFCSP AND SOIC
1.0
0.5
0.0
–40
–20
0
20
40
60
80
100
120
AMBIENT TEMPERATURE (°C)
Figure 4. Maximum Power Dissipation
ESD CAUTION
ESD (electrostatic discharge) sensitive device. Electrostatic charges as high as 4000 V readily accumulate on
the human body and test equipment and can discharge without detection. Although this product features
proprietary ESD protection circuitry, permanent damage may occur on devices subjected to high energy
electrostatic discharges. Therefore, proper ESD precautions are recommended to avoid performance
degradation or loss of functionality.
Rev. B | Page 5 of 28
AD8099
TYPICAL PERFORMANCE CHARACTERISTICS
Default Conditions: VS = 5 V, TA = 25°C, RL = 1 kΩ tied to ground unless otherwise noted. Refer to Figure 63 through Figure 66 for
component values and gain configurations.
4
3
4
3
G = +2
G = +2
V
V
R
= 0.2V p-p
= ±5V
V
V
R
= 0.2V p-p
= ±5V
OUT
OUT
S
S
G = +5
= 1kΩ
= 1kΩ
LOAD
2
LOAD
2
1
1
0
0
–1
–2
–3
–4
–5
–6
–7
–8
–9
–10
–1
–2
–3
–4
–5
–6
–7
–8
–9
–10
G = +20
G = +20
G = +5
G = +10
G = –1
G = –1
G = +10
1
10
100
FREQUENCY (MHz)
1000
1
10
100
FREQUENCY (MHz)
1000
Figure 5. Small Signal Frequency Response for Various Gains (SOIC)
Figure 8. Small Signal Frequency Response for Various Gains (CSP)
17
17
R
= 1kΩ, CSP
G = +5
G = +5
L
V
V
= ±5V
R = 1kΩ
S
R
= 100Ω, CSP
L
16
15
14
13
12
11
10
9
16
15
14
13
12
11
10
9
L
= 0.2V p-p
V
= 0.2V p-p
OUT
OUT
V
= ±5V, SOIC
= ±2.5V, CSP
S
R
= 1kΩ, SOIC
L
V
S
R
= 100Ω, SOIC
L
V
= ±5V, CSP
S
8
8
V
= ±2.5V, SOIC
100
S
7
7
1
10
100
1000
1
10
1000
FREQUENCY (MHz)
FREQUENCY (MHz)
Figure 6. Small Signal Frequency Response for Various Load Resistors
Figure 9. Small Signal Frequency Response for Various Supply Voltages
11
11
V
= 0.2V p-p
+125°C
V
= 0.2V p-p
OUT
OUT
+125°C
+85°C
10
9
8
7
6
5
4
3
2
1
10
9
8
7
6
5
4
3
2
1
+85°C
–40°C
+25°C
–40°C
+25°C
G = +2
= ±5V
G = +2
= ±5V
V
V
S
S
R
= 1kΩ
R
= 1kΩ
L
L
1
10
100
FREQUENCY (MHz)
1000
1
10
100
1000
FREQUENCY (MHz)
Figure 7. Small Signal Frequency Response for Various Temperatures (SOIC)
Figure 10. Small Signal Frequency Response for Various Temperatures (CSP)
Rev. B | Page 6 of 28
AD8099
20
19
18
17
16
15
14
13
12
11
10
9
90
80
70
60
50
40
30
20
10
0
–30
5pF, CSP
G = +5
= ±5V
V
S
–45
MAGNITUDE
–60
–75
–90
PHASE
–105
–120
–135
–150
–165
–180
1pF, SOIC
1pF, CSP
V
R
= ±5V
= 1kΩ
S
5pF, SOIC
100
L
UNCOMPENSATED
–10
0.001
1
10
FREQUENCY (MHz)
1000
0.01
0.1
1.0
10
100
1000
FREQUENCY (MHz)
Figure 11. Small Signal Frequency Response for Various Capacitive Loads
Figure 14. Open Loop Frequency Response
1
2
1
G = +2
G = +10
G = +2
0
–1
G = +10
0
–2
–1
–2
–3
–4
–5
–6
–7
–8
–9
G = +20
–3
–4
G = +20
G = +5
–5
–6
–7
–8
G = +5
V
V
R
= ±5V
S
V
V
= ±5V
S
–9
= 2V p-p
OUT
= 2V p-p
OUT
= 1kΩ
LOAD
R
= 1kΩ
LOAD
–10
1
10
100
1000
1
10
100
1000
FREQUENCY (MHz)
FREQUENCY (MHz)
Figure 12. Large Signal Frequency Response for Various Gains (SOIC)
Figure 15. Large Signal Frequency Response for Various Gains (CSP)
6.5
6.5
V
= ±5V
V
= 1.4V p-p
V
= ±5V
V
= 1.4V p-p
S
OUT
S
OUT
G = +2
R
G = +2
R
6.4
6.3
6.2
6.1
6.0
5.9
5.8
5.7
5.6
5.5
6.4
6.3
6.2
6.1
6.0
5.9
5.8
5.7
5.6
5.5
= 150Ω
= 150Ω
L
L
V
= 200mV p-p
OUT
V
= 200mV p-p
OUT
1
10
100
1
10
100
FREQUENCY (MHz)
FREQUENCY (MHz)
Figure 13. 0.1 dB Flatness (SOIC)
Figure 16. 0.1 dB Flatness (CSP)
Rev. B | Page 7 of 28
AD8099
15
14
13
12
11
10
9
15
14
13
12
11
10
9
V
= ±5V, CSP
R
= 1kΩ, CSP
S
L
V
= ±2.5V, CSP
S
R
= 100Ω, CSP
L
R
= 100Ω, SOIC
L
V
= ±5V, SOIC
S
8
8
R
= 1kΩ, SOIC
L
7
7
V
= ±2.5V, SOIC
S
G = +5
G = +5
6
5
6
R
V
= 1kΩ
OUT
V
V
= ±5V
L
S
= 2V p-p
= 2V p-p
OUT
5
1
10
100
1000
1
10
100
1000
FREQUENCY (MHz)
FREQUENCY (MHz)
Figure 17. Large Signal Frequency Response for Various Load Resistances
Figure 20. Large Signal Frequency Response for Various Supply Voltages
100.0
10.0
1.0
–10
G = +2
R
= 1kΩ
= ±5V
L
–20
–30
–40
–50
–60
–70
–80
–90
V
V
S
= 0V
DIS
CSP
SOIC
0.1
0.01
V
= ±5V
S
G = +2
0.001
1
10
100
1000
0.1
1
10
FREQUENCY (MHz)
100
1000
FREQUENCY (MHz)
Figure 18. Input Impedance vs. Frequency
Figure 21. Off Isolation vs. Frequency
100
10
–50
–60
G = +5
V
V
= 2V p-p
OUT
= ±5V
S
G = +5
R
= 100Ω
L
–70
–80
SOIC
G = +10
G = +2
1
–90
–100
–110
–120
0.1
CSP
SOLID LINES – SECOND HARMONICS
DOTTED LINES–THIRDHARMONICS
V
= ±5V
S
0.01
0.1
1
10
FREQUENCY (MHz)
100
1000
0.1
1.0
FREQUENCY (MHz)
10.0
Figure 19. Output Impedance vs. Frequency for Various Gains
Figure 22. Harmonic Distortion vs. Frequency
Rev. B | Page 8 of 28
AD8099
–50
–60
–50
–60
G = +5
G = +5
V
V
= 2V p-p
V
V
= 2V p-p
OUT
= ±5V
OUT
= ±5V
S
S
R
= 1kΩ
R = 1kΩ
L
L
–70
–70
–80
–80
–90
–90
–100
–110
–120
–130
–100
–110
–120
–130
SOLID LINE – SECOND HARMONIC
DOTTED LINE – THIRD HARMONIC
SOLID LINE – SECOND HARMONIC
DOTTED LINE – THIRD HARMONIC
0.1
1.0
FREQUENCY (MHz)
10.0
0.1
1.0
10.0
FREQUENCY (MHz)
Figure 23. Harmonic Distortion vs. Frequency (SOIC)
Figure 26. Harmonic Distortion vs. Frequency (CSP)
–40
–50
–40
–50
G = +2
G = +2
V
V
= 2V p-p
V
V
= 2V p-p
OUT
= ±5V
OUT
= ±5V
S
S
R
= 1kΩ
R = 1kΩ
L
L
–60
–60
–70
–70
–80
–80
–90
–90
–100
–110
–120
–130
–100
–110
–120
–130
SOLIDLINE–SECONDHARMONIC
DOTTEDLINE–THIRDHARMONIC
SOLID LINE – SECOND HARMONIC
DOTTED LINE – THIRD HARMONIC
0.1
1.0
FREQUENCY (MHz)
10.0
0.1
1.0
FREQUENCY (MHz)
10.0
Figure 24. Harmonic Distortion vs. Frequency (SOIC)
Figure 27. Harmonic Distortion vs. Frequency (CSP)
–40
–50
–40
–50
G = –1
G = –1
V
V
= 2V p-p
V
V
= 2V p-p
OUT
= ±5V
OUT
= ±5V
S
S
R
= 1kΩ
R = 1kΩ
L
L
–60
–60
–70
–70
–80
–80
–90
–90
–100
–110
–120
–130
–100
–110
–120
–130
SOLID LINE – SECOND HARMONIC
DOTTED LINE – THIRD HARMONIC
SOLID LINE – SECOND HARMONIC
DOTTED LINE – THIRD HARMONIC
0.1
1.0
FREQUENCY (MHz)
10.0
0.1
1.0
FREQUENCY (MHz)
10.0
Figure 25. Harmonic Distortion vs. Frequency (SOIC)
Figure 28. Harmonic Distortion vs. Frequency (CSP)
Rev. B | Page 9 of 28
AD8099
–50
–50
–60
G = +10
= 1kΩ
G = +10
R = 1kΩ
L
R
L
–60
–70
V
V
= ±2.5V
V
V
= ±2.5V
S
S
= 1V p-p
= 1V p-p
OUT
OUT
–70
–80
–80
–90
–90
–100
–110
–120
–100
–110
–120
V
V
= ±5V
S
V
V
= ±5V
S
= 2V p-p
OUT
= 2V p-p
OUT
SOLID LINES – SECOND HARMONICS
DOTTED LINES – THIRD HARMONICS
SOLID LINES – SECOND HARMONICS
DOTTED LINES–THIRDHARMONICS
0.1
1.0
FREQUENCY (MHz)
10.0
0.1
1.0
10.0
FREQUENCY (MHz)
Figure 29. Harmonic Distortion vs. Frequency and Supply Voltage (SOIC)
Figure 32. Harmonic Distortion vs. Frequency for Various Supplies (CSP)
–40
–40
G = +5
G = +5
V
= ±5V
V = ±5V
S
S
f = 10MHz
f = 10MHz
–50
–60
–50
–60
R
= 100Ω
R
= 100Ω
L
L
–70
–70
–80
–80
–90
–90
–100
–110
–100
–110
SOLID LINE – SECOND HARMONIC
DOTTED LINE – THIRD HARMONIC
SOLID LINE – SECOND HARMONIC
DOTTED LINE – THIRD HARMONIC
1
2
3
4
5
6
7
1
2
3
4
5
6
7
OUTPUT AMPLITUDE (V p-p)
OUTPUT AMPLITUDE (V p-p)
Figure 30. Harmonic Distortion vs. Output Amplitude (SOIC)
Figure 33. Harmonic Distortion vs. Output Amplitude (CSP)
–40
–40
G = +5
= ±5V
G = +5
V = ±5V
S
f = 10MHz
R = 1kΩ
L
V
S
–50
–60
–50
f = 10MHz
= 1kΩ
R
L
–60
–70
–70
–80
–80
–90
–90
–100
–110
–120
–100
–110
–120
SOLID LINE – SECOND HARMONIC
DOTTED LINE – THIRD HARMONIC
SOLID LINE – SECOND HARMONIC
DOTTED LINE – THIRD HARMONIC
1
2
3
4
5
6
7
1
2
3
4
5
6
7
OUTPUT AMPLITUDE (V p-p)
OUTPUT AMPLITUDE (V p-p)
Figure 31. Harmonic Distortion vs. Output Amplitude (SOIC)
Figure 34. Harmonic Distortion vs. Output Amplitude (CSP)
Rev. B | Page 10 of 28
AD8099
0.20
0.15
0.10
0.05
0
0.20
0.15
0.10
0.05
0
10pF, 20Ω R
SNUB
10pF, 20Ω R
SNUB
1pF
1pF
–0.05
–0.10
–0.15
–0.20
–0.05
–0.10
–0.15
–0.20
R
R
SNUB
SNUB
C
R
C
R
L
L
L
L
G = +5
G = +5
V
= ±5V
V
= ±5V
S
S
R
= 1kΩ
R
= 1kΩ
L
L
0
5
10
15
20
25
TIME (ns)
30
35
40
45
50
0
5
10
15
20
25
TIME (ns)
30
35
40
45
50
Figure 35. Small Signal Transient Response for Various Capacitive Loads
(SOIC)
Figure 38. Small Signal Transient Response for Various Capacitive Loads
(CSP)
0.15
0.20
V
= ±5.0V
V
CSP
= ±2.5V
S
S
AND ±2.5V, CSP
V
= ±5.0V
S
0.15
CSP
0.10
0.05
0
0.10
0.05
0
V
SOIC
= ±5.0V
S
–0.05
–0.10
–0.05
–0.10
–0.15
V
= ±2.5V
SOIC
S
V
= ±5.0V
S
R
= 1kΩ, 100Ω
= 200mV p-p
–0.15
–0.20
L
AND ±2.5V, SOIC
G = +10
= 1kΩ
V
OUT
R
L
G = +5
0
10
20
30
40
50
0
10
20
30
40
50
TIME (ns)
TIME (ns)
Figure 36. Small Signal Transient Response for Various Supply Voltages
Figure 39. Small Signal Transient Response for Various Supply Voltages
5
3.5
INPUT × 2
TURN OFF
INPUT
TURN ON
INPUT
4
3.0
2.5
2.0
1.5
1.0
0.5
0
3
R
= 100Ω
L
2
1
0
V
= ±5V
G = 2
S
–1
–2
–3
–4
–5
R
= 1kΩ
L
TURN ON
TURN OFF
–0.5
0
100 200 300 400 500 600 700 800 900 1000
TIME (ns)
0
50
100
TIME (ns)
150
200
Figure 40. Disable/Enable Switching Speed
Figure 37. Output Overdrive Recovery for Various Resistive Loads
Rev. B | Page 11 of 28
AD8099
1.5
1.0
0.5
0
1.5
1.0
0.3%
0.2%
0.1%
0%
OUTPUT
INPUT
V
= ±2.5V
S
0.5
0
ERROR
–0.5
–1.0
–0.5
–1.0
–1.5
–0.1%
–0.2%
–0.3%
G = +2
G = +10
= 1kΩ
R
V
= 1kΩ
LOAD
V
= ±5.0V
30
S
R
= ±5V
L
s
–1.5
0
10
20
40
50
0
5
10
15
20
25
30
35
40
45
TIME (ns)
TIME (ns)
Figure 41. Large Signal Transient Response vs. Supply Voltage (CSP)
Figure 44. Short Term Settling Time (CSP)
1.5
1.5
1.0
0.3%
0.2%
0.1%
0%
V
= ±5.0V
S
OUTPUT
INPUT
1.0
0.5
V
= ±2.5V
S
0.5
0
0
ERROR
–0.5
–1.0
–1.5
–0.5
–1.0
–1.5
–0.1%
–0.2%
–0.3%
G = +2
G = +10
= 1kΩ
R
= 1kΩ
LOAD
R
V = ±5V
L
s
0
10
20
30
40
50
0
5
10
15
20
25
30
35
40
45
TIME (ns)
TIME (ns)
Figure 45. Short Term Settling Time (SOIC)
Figure 42. Large Signal Frequency Response vs. Supply Voltage (SOIC)
1.5
1.0
0.30%
0.20%
0.10%
0%
1.5
V
= ±5V
G = +2
= ±5V
S
OUTPUT
V
S
1.0
0.5
INPUT
V
= ±2.5V
S
0.5
0
0
ERROR
–0.5
–1.0
–1.5
–0.10%
–0.20%
–0.30%
–0.5
–1.0
–1.5
R
= 1kΩ, 100Ω
L
G = +5
0
50
100 150 200 250 300 350 400 450 500
0
10
20
30
40
50
TIME (µs)
TIME (ns)
Figure 43. Large Signal Transient Response for Various Supply Voltages and
Load Resistances (SOIC and CSP)
Figure 46. Long Term Settling Time
Rev. B | Page 12 of 28
AD8099
–20
–30
–40
–50
–60
–70
–80
–90
–100
–110
0
–10
–20
–30
–40
–50
–60
–70
–80
–90
–100
G = +5
= 1kΩ
G = +2
= 1kΩ
R
R
L
L
NEGATIVE
POSITIVE
0.1
1.0
10
100
1000
0.01
0.10
1.0
10
100
1000
FREQUENCY (MHz)
FREQUENCY (MHz)
Figure 47. Common-Mode Rejection vs. Frequency
Figure 50. Power Supply Rejection vs. Frequency
1000
100
10
1000
100
10
1
1
1
10
100
1k
10k 100k 1M
FREQUENCY (Hz)
10M 100M 1G
1
10
100
1k
10k 100k 1M
FREQUENCY (Hz)
10M 100M 1G
DISABLE
Figure 51. Input Current Noise vs. Frequency (
= +VS)
DISABLE
Figure 48. Input Current Noise vs. Frequency (
= Open)
1000
V
= ±5V
S
N = 1,200
X = –70µV
120
σ
= 80µV
100
80
60
40
20
0
10
1
0.1
1
10
100
1k
10k 100k 1M
FREQUENCY (Hz)
10M 100M 1G
–300
–200
–100
0
100
200
V
(µV)
OFFSET
Figure 49. Input Voltage Noise vs. Frequency
Figure 52. Input Offset Voltage Distribution
Rev. B | Page 13 of 28
AD8099
400
300
200
100
0
20
18
16
14
12
10
8
V
= 5V
S
V
= ±5V
= 5V
S
V
S
V
= ±5V
S
–100
–200
–40 –25 –10
5
20
35
50
65
80
95 110 125
–40 –25 –10
5
20
35
50
65
80
95 110 125
TEMPERATURE (C)
TEMPERATURE (C)
Figure 53. Input Offset Voltage vs. Temperature
Figure 56. Supply Current vs. Temperature
–5.4
–5.6
–5.8
1.0
0.8
I
+, V = ±5V
S
B
I
+, V = ±5V
S
B
0.6
0.4
0.2
I
–, V = ±5V
S
B
I
–, V = ±5V
S
–6.0
–6.2
–6.4
–6.6
0
B
I
+, V = 5V
S
B
–0.2
–0.4
–0.6
–0.8
–1.0
I
–, V = 5V
S
B
I
–, V = 5V
S
B
I
+, V = 5V
S
B
–40 –25 –10
5
20
35
50
65
80
95 110 125
–40 –25 –10
5
20
35
50
65
80
95 110 125
TEMPERATURE (C)
TEMPERATURE (C)
DISABLE
DISABLE
Pin = +VS)
Figure 54. Input Bias Current vs. Temperature (
Pin Floating)
Figure 57. Input Bias Current vs. Temperature (
1.24
–V + V
S
OUT
1.22
1.20
1.18
1.16
1.14
1.12
V
= ±5V
S
+V – V
S
OUT
–V + V
S
OUT
+V – V
S
OUT
V
= 5V
S
–40 –25 –10 –5
20
35
50
65
80
95 110 125
TEMPERATURE (C)
Figure 55. Output Saturation Voltage vs. Temperature
Rev. B | Page 14 of 28
AD8099
THEORY OF OPERATION
The AD8099 is a voltage feedback op amp that employs a new
highly linear low noise input stage. With this input stage, the
AD8099 can achieve better than 90 dB distortion for a 2 V p-p,
10 MHz output signal with an input referred voltage noise of
output and self-inductance of the package and bond wire from
the feedback loop. While using the secondary output for feed-
back, inductance in the primary output will now help to isolate
capacitive loads from the output impedance of the amplifier.
Since the SOIC has greater inductance in its output, the SOIC
will drive capacitive loads better than the LFCSP. Using the
primary output for feedback with both packages will result in
the LFCSP driving capacitive load better than the SOIC.
less than 1 nV/√ . This noise level and distortion
Hz
performance has been previously achievable only with fully
uncompensated amplifiers. The AD8099 achieves this level of
performance for gains as low as +2. This new input stage also
triples the achievable slew rate for comparably compensated 1
The LFCSP and SOIC pinouts are identical, except for the
rotation of all pins counterclockwise by one pin on the LFCSP.
This isolates the inputs from the negative power supply pin,
removing a mutually inductive coupling that is most prominent
while driving heavy loads. For this reason, the LFCSP second
harmonic, while driving a heavy load, is significantly better
than that of the SOIC.
nV/√ amplifiers.
Hz
The simplified AD8099 topology is shown in Figure 58. The
amplifier is a single gain stage with a unity gain output buffer
fabricated in Analog Devices’ extra fast complimentary bipolar
process (XFCB). The AD8099 has 85 dB of open-loop gain and
maintains precision specifications such as CMRR, PSRR, VOS,
and ∆VOS/∆T to levels that are normally associated with
topologies having two or more gain stages.
A three-state input pin is provided on the AD8099 for a high
impedance power-down and an optional input bias current
cancellation circuit. The high impedance output allows several
AD8099s to drive the same ADC or output line time inter-
V
gm
BUFFER
OUT
leaved. Pulling the
pin low activates the high
DISABLE
R1
R
L
C
C
impedance state. See Table 5 for threshold levels. When the
pin is left floating, the AD8099 operates normally.
DISABLE
With the
Figure 58. AD8099 Topology
pin pulled within 0.7 V of the positive
DISABLE
The AD8099 can be externally compensated down to a gain of 2
through the use of an RC network. Above gains of 15, no exter-
nal compensation network is required. To realize the full gain
bandwidth product of the AD8099, no PCB trace should be
connected to or within close proximity of the external compen-
sation pin for the lowest possible capacitance.
supply, an optional input bias current cancellation circuit is
turned on, which lowers the input bias current to less than 200
nA. In this mode, the user can drive the AD8099 with a high dc
source impedance and still maintain minimal output referred
offset without having to use impedance matching techniques. In
addition, the AD8099 can be ac-coupled while setting the bias
point on the input with a high dc impedance network. The
input bias current cancellation circuit will double the input
referred current noise, but this effect is minimal as long as
wideband impedance is kept low (see Figure 48 and Figure 51).
External compensation allows the user to optimize the closed-
loop response for minimal peaking while increasing the gain
bandwidth product in higher gains, lowering distortion errors
that are normally more prominent with internally compensated
parts in higher gains. For a fixed gain bandwidth, wideband
distortion products would normally increase by 6 dB going
from a closed-loop gain of 2 to 4. Increasing the gain bandwidth
product of the AD8099 eliminates this effect with increasing
closed-loop gain.
A pair of internally connected diodes limits the differential
voltage between the noninverting input and the inverting input
of the AD8099. Each set of diodes has two series diodes, which
are connected in anti-parallel. This limits the differential
voltage between the inputs to approximately ±1.8 V. All of the
AD8099 pins are ESD protected with voltage limiting diodes
connected between both rails. The protection diodes can handle
5 mA of steady state current. Currents should be limited to 5
mA or less through the use of a series limiting resistor.
The AD8099 is available in both a SOIC and an LFCSP, each of
which has a thermal pad for lower operating temperature. To
help avoid this pad in board layout, both packages have an extra
output pin on the opposite side of the package for ease in con-
necting a feedback network to the inputs. The secondary output
pin also isolates the interaction of any capacitive load on the
Rev. B | Page 15 of 28
AD8099
APPLICATIONS
CF—Creates a zero in the loop response to compensate the pole
created by the input capacitance (including stray capacitance)
and the feedback resistor RF. CF helps reduce high frequency
peaking and ringing in the closed-loop response. Typical range
is 0.5 pF to 1.5 pF for evaluation circuits used here.
USING THE AD8099
The AD8099 offers unrivaled noise and distortion performance
in low signal gain configurations. In low gain configurations
(less than15), the AD8099 requires external compensation. The
amount of gain and performance needed will determine the
compensation network.
R1—This resistor terminates the input of the amplifier to the
source resistance of the signal source, typically 50 Ω. (This is
application specific and not always required.)
Understanding the subtleties of the AD8099 gives the user
insight on how to exact its peak performance. Use the
component values and circuit configurations shown in the
Applications section as starting points for designs. Specific
circuit applications will dictate the final configuration and value
of your components.
RS—Many high speed amplifiers in low gain configurations
require that the input stage be terminated into a nominal
impedance to maintain stability. The value of RS should be kept
to 50 Ω or lower to maintain low noise performance. At higher
gains, RS may be reduced or even eliminated. Typical range is
0 Ω to 50 Ω.
CIRCUIT COMPONENTS
The circuit components are referenced in Figure 59, the
recommended noninverting circuit schematic for the AD8099.
See Table 4 for typical component values and performance data.
CC—The compensation capacitor decreases the open-loop gain
at higher frequencies where the phase is degrading. By decreas-
ing the open-loop gain here, the phase margin is increased and
the amplifier is stabilized. Typical range is 0 pF to 5 pF. The
value of CC is gain dependent.
C
F
+V
S
C2
10µF
R
F
C3
RC—The series lead inductance of the package and the com-
pensation capacitance (CC) forms a series resonant circuit. RC
dampens this resonance and prevents oscillations. The
recommended value of RC is 50 Ω for a closed-loop gain of 2.
This resistor introduces a zero in the open-loop response and
must be kept low so that this zero occurs at a higher frequency.
The purpose of the compensation network is to decrease the
open-loop gain. If the resistance becomes too large, the gain will
be reduced to the resistor value, and not necessarily to 0 Ω,
which is what a single capacitor would do over frequency.
Typical value range is 0 Ω to 50 Ω.
0.1µF
1
R
G
2
7
6
AD8099
V
OUT
R
S
5
V
3
IN
4
8
R1
DISABLE
R
C1
C
C5
0.1µF
C
C4
C
10µF
–V
S
C1—To lower the impedance of RC , C1 is placed in parallel with
RC. C1 is not required, but greatly reduces peaking at low
closed-loop gains. The typical value range is 0 pF to 2 pF.
Figure 59. Wideband Noninverting Gain Configuration (SOIC)
RF and RG—The feedback resistor and the gain set resistor
determine the noise gain of the amplifier; typical RF values
range from 250 Ω to 499 Ω.
C2 and C3—Bypass capacitors are connected between both
supplies for optimum distortion and PSRR performance. These
capacitors should be placed as close as possible to the supply
pins of the amplifier. For C3, C5, a 0508 case size should be
used. The 0508 case size offers reduced inductance and better
frequency response.
C4 and C2—Electrolytic bypass capacitors.
Rev. B | Page 16 of 28
AD8099
RECOMMENDED VALUES
Table 4. Recommended Values and AD8099 Performance
Feedback
Network Values Network Values
Compensation
−3 dB SS
Bandwidth
Output Noise Total Output Noise
(AD8099 Only) Including Resistors
Slew Rate
(V/µs)
Peaking
(dB)
(nV/√Hz)
(nV/√Hz)
Gain Package
(MHz)
RF RG RS CF RC
250 250 50 1.5 50
250 250 50 0.5 50
250 250 50 1.0 50
CC
4
C1
1.5
2
−1, 2
2
SOIC
CSP
CSP
440/700
700
515
475
0.3/3.1
3.2
2.1
2.1
2.1
4.9
9.6
19
4
4
5
−1
5
5
2
420
475
0.8
4
CSP/SOIC 499 124 20 0.5 50
1
0
510
735
1.4
8.6
13.3
23.3
10 CSP/SOIC 499 54
20 CSP/SOIC 499 26
0
0
0
0
0
0
0.5
0
0
550
1350
1450
0.8
0
160
0
CIRCUIT CONFIGURATIONS
Figure 60 through Figure 66 show typical schematics for the
AD8099 in various gain configurations. Table 4 data was
collected using the schematics shown in Figure 60 through
Figure 66. Resistor R1, as shown in Figure 60 through Figure 66,
is the test equipment termination resistor. R1 is not required for
normal operation, but is shown in the schematics for
completeness.
C
F
C
F
1.5pF
1pF
+V
+V
S
C2
S
C2
10µF
10µF
R
250Ω
R
250Ω
F
F
C3
C3
0.1µF
0.1µF
R
250Ω
R
250Ω
G
G
2
1
V
3
V
2
8
7
IN
IN
R1
50Ω
R
S
50Ω
R
S
50Ω
R1
50Ω
7
6
V
OUT
AD8099
AD8099
V
OUT
R
1kΩ
6
RL
5
L
4
3
5
4
1kΩ
1
8
C1
1.5pF
R
C
50Ω
R
C
50Ω
C1
2pF
DISABLE
DISABLE
C5
C5
0.1µF
0.1µF
C
5pF
C
C
C
4pF
C4
10µF
C4
10µF
–V
S
–V
S
Figure 62. Amplifier Configuration for CSP Package, Gain =–1
Figure 60. Amplifier Configuration for SOIC Package, Gain = –1
C
F
0.5pF
C
F
1.5pF
+V
+V
S
C2
S
C2
10µF
10µF
R
250Ω
R
250Ω
F
F
C3
C3
0.1µF
0.1µF
R
250Ω
R
250Ω
G
G
2
1
3
2
8
7
R
S
50Ω
R
S
50Ω
7
6
AD8099
V
OUT
AD8099
V
OUT
R
1kΩ
R
1kΩ
6
5
L
L
V
4
V
3
IN
IN
5
4
R1
50Ω
R1
50Ω
1
8
C1
1.5pF
C1
2pF
R
C
50Ω
R
C
50Ω
DISABLE
DISABLE
C5
C5
0.1µF
0.1µF
C
C
5pF
C
C
4pF
C4
10µF
C4
10µF
–V
S
–V
S
Figure 61. Amplifier Configuration for SOIC Package, Gain = +2
Figure 63. Amplifier Configuration for CSP Package, Gain = +2
Rev. B | Page 17 of 28
AD8099
C
0.5pF
+V
F
S
C2
10µF
+V
S
C2
10µF
R
499Ω
F
R
499Ω
F
C3
0.1µF
R
26Ω
C3
0.1µF
G
FB
R
G
–
+V
FB
124Ω
VO
–
AD8099
V
OUT
+V
CC
R
1kΩ
L
R
S
V
IN
VO
+
AD8099
V
OUT
–V
D
20Ω
CC
R
L
1kΩ
R1
50Ω
V
+
IN
–V
D
R1
50Ω
DISABLE
R
C
50Ω
C5
0.1µF
DISABLE
C5
0.1µF
C4
10µF
C
C
1pF
C4
10µF
–V
S
–V
S
Figure 66. Amplifier Configuration for CSP and SOIC Packages, Gain = +20
Figure 64. Amplifier Configuration for CSP and SOIC Package, Gain = +5
+V
S
C2
10µF
R
F
499Ω
C3
0.1µF
R
54Ω
G
FB
–
+V
VO
V
AD8099
OUT
CC
R
L
V
+
IN
1kΩ
–V
D
R1
50Ω
DISABLE
C5
0.1µF
C
0.5pF
C
C4
10µF
–V
S
Figure 65. Amplifier Configuration for CSP and SOIC Packages, Gain = +10
Rev. B | Page 18 of 28
AD8099
PERFORMANCE VS. COMPONENT VALUES
The influence that each component has on the AD8099
frequency response can be seen in Figure 67 and Figure 68. In
Figure 67 and Figure 68, all component values are held
constant, except for the individual component shown, which is
varied. For example, in the RS performance plot of Figure 68, all
components are held constant except RS, which is varied from
0 Ω to 50 Ω.; and clearly indicates that RS has a major influence
on peaking and bandwidth of the AD8099.
C
F
9
8
+V
S
C2
10µF
C1 = 0pF
R
F
7
C3
0.1µF
6
1
R
G
5
2
7
6
AD8099
V
OUT
4
R
S
5
3
V
IN
4
3
8
R1
DISABLE
2
R
C1
C
1
C5
C1 = 1.5pF
C1 = 2pF
0.1µF
V
= ±5V
0
S
G = +2
R
SOIC PACKAGE
C
C4
10µF
C
–1
–2
= 1kΩ
LOAD
1
10
100
FREQUENCY (MHz)
1000
3000
–V
S
SOIC PINOUT SHOWN
10
9
10
9
V
= ±5V
V
= ±5V
C
= 3pF
= 4pF
S
S
C
G = +2
R
SOIC PACKAGE
G = +2
R
SOIC PACKAGE
= 1kΩ
= 1kΩ
LOAD
LOAD
8
8
C
C
7
7
6
6
R = 50Ω
C
5
5
C
= 5pF
C
4
4
3
3
2
2
R
= 20Ω
C
1
1
0
0
R
= 35Ω
C
–1
–1
1
10
100
FREQUENCY (MHz)
1000
3000
1
10
100
1000
3000
FREQUENCY (MHz)
Figure 67. Frequency Response for Various Values of C1, CC, RC
Rev. B | Page 19 of 28
AD8099
10
9
10
9
R
= R = 200
G
F
C
= 0.5pF
F
8
8
7
7
6
6
C
= 1pF
F
5
5
R
= R = 300
G
F
C
= 1.5pF
F
4
4
R
= R = 250
G
F
3
3
2
2
1
1
V
= ±5V
V
= ±5V
S
S
G = +2
R
SOIC PACKAGE
G = +2
R
SOIC PACKAGE
0
0
= 1kΩ
= 1kΩ
LOAD
LOAD
–1
–1
1
10
100
FREQUENCY (MHz)
1000
3000
1
10
100
FREQUENCY (MHz)
1000
3000
C
F
+V
S
C2
10µF
12
11
10
9
R
= 0
S
R
F
C3
0.1µF
1
R
G
2
7
8
6
AD8099
V
OUT
R
S
5
3
7
V
IN
4
8
6
R1
DISABLE
R
= 50
S
R
C1
C
5
C5
0.1µF
4
3
R
= 20
C
C
S
C4
10µF
V
= ±5V
2
S
G = +2
1
R
= 1kΩ
LOAD
SOIC PACKAGE
0
–V
S
1
10
100
FREQUENCY (MHz)
1000
10000
SOIC PINOUT SHOWN
Figure 68. Frequency Response for Various Values of RF, CF, RS
TOTAL OUTPUT NOISE CALCULATIONS AND DESIGN
To analyze the noise performance of an amplifier circuit, the
individual noise sources must be identified. Then determine if
the source has a significant contribution to overall noise perfor-
mance of the amplifier. To simplify the noise calculations, we
will work with noise spectral densities, rather than actual
voltages to leave bandwidth out of the expressions (noise
noise at the output. Noise is generally specified RTI (referred to
input), but it is often simpler to calculate the noise referred to
the output (RTO) and then divide by the noise gain to obtain
the RTI noise.
All resistors have a Johnson noise of √
, where k is
(4kBTR)
Boltzmann’s Constant (1.38 × 10–23 J/K), T is the absolute
temperature in Kelvin, B is the bandwidth in Hz, and R is the
resistance in ohms. A simple relationship, which is easy to
remember, is that a 50 Ω resistor generates a Johnson noise of
spectral density, which is generally expressed in nV/√ , is
Hz
equivalent to the noise in a 1 Hz bandwidth).
The noise model shown in Figure 69 has six individual noise
sources: the Johnson noise of the three resistors, the op amp
voltage noise, and the current noise in each input of the
amplifier. Each noise source has its own contribution to the
1 nV√ at 25°C. The AD8099 amplifier has roughly the same
Hz
equivalent noise as a 50 Ω resistor.
Rev. B | Page 20 of 28
AD8099
V
N, R2
R2
For RTO calculations, the input offset voltage and the voltage
GAIN FROM
"A" TO OUTPUT
=
generated by the bias current flowing through R3 are multiplied
by the noise gain of the amplifier. The voltage generated by IB–
through R2 is summed together with the previous offset
voltages to arrive at a final output offset voltage. The offset
voltage can also be referred to the input (RTI) by dividing the
calculated output offset voltage by the noise gain.
4kTR2
NOISE GAIN =
V
I
N, R1
N–
R2
R1
B
A
R1
R3
NG = 1 +
V
N
4kTR1
V
V
OUT
N, R3
I
N+
GAIN FROM
"B" TO OUTPUT
R2
R1
= –
4kTR3
As seen in Figure 70 if IB+ and IB– are the same and R3 equals the
parallel combination of R1 and R2, then the RTI offset voltage
can be reduced to only VOS. This is a common method used to
reduce output offset voltage. Keeping resistances low helps to
minimize offset error voltage and keeps the voltage noise low.
2
R2
R1 + R2
2
2
V
+ 4kTR3 + 4kTR1
N
2
2
R1 × R2
2
R1
R1 + R2
2
RTI NOISE =
+I
R3 + I
+ 4kTR2
N+
N–
R1 + R2
RTO NOISE = NG × RTI NOISE
Figure 69. Op Amp Noise Analysis Model
PIN AND INPUT BIAS CANCELLATION
DISABLE
The AD8099
pin performs three functions; enable,
DISABLE
disable, and reduction of the input bias current. When the
pin is brought to within 0.7 V of the positive supply,
In applications where noise sensitivity is critical, care must be
taken not to introduce other significant noise sources to the
amplifier. Each resistor is a noise source. Attention to the
following areas is critical to maintain low noise performance:
design, layout, and component selection. A summary of noise
performance for the amplifier and associated resistors can be
seen in Table 4.
DISABLE
the input bias current is reduced by an approximate factor of 60.
However, the input current noise doubles to 5.2 pA/√ . Table
Hz
5 outlines the
pin functionality.
DISABLE
Table 5.
Pin Truth Table
DISABLE
Supply Voltage
5 V
+5 V
INPUT BIAS CURRENT AND DC OFFSET
Disable
Enable
Low Input Bias Current
–5 to +2.4
Open
4.3 to 5
0 to 2.4
Open
4.3 to 5
In high noise gain configurations, the effects of output offset
voltage can be significant, even with low input bias currents and
input offset voltages. Figure 70 shows a comprehensive offset
voltage model, which can be used to determine the referred to
output (RTO) offset voltage of the amplifier or referred to input
(RTI) offset voltage.
R2
GAIN FROM
=
"A" TO OUTPUT
NOISE GAIN =
I
B–
R2
R1
B
A
R1
R3
NG = 1 +
V
OS
V
OUT
I
B+
GAIN FROM
"B" TO OUTPUT
R2
R1
= –
R2
R1
R2
R1
OFFSET (RTO) = V
1 +
+ I × R3 1 +
B+
– I × R2
B–
OS
R1 × R2
OFFSET (RTI) = V + I × R3 – I
B–
OS
B+
R1 + R2
FOR BIAS CURRENT CANCELLATION:
R1 × R2
OFFSET (RTI) = V
IF I = I AND R3 =
B+ B–
OS
R1 + R2
Figure 70. Op Amp Total Offset Voltage Model
Rev. B | Page 21 of 28
AD8099
AVDD
DVDD
0.1µF
0.1µF
REF
AGND AVDD DGND
DVDD
+V
REF
S
C1
10µF
R
F
150Ω
1µF
47µF
C2
AD7667
0.1µF
R
150Ω
G
REFGND
1
R7
15Ω
2
7
R
50Ω
S
6
IN
AD8099
5
INGND
3
V
IN
C6
4
2.7nF
8
C1
R
C
2pF
50Ω
DISABLE
C
9pF
C
C4
10µF
+2.5V
R1
590Ω
R2
590Ω
C5
0.1µF
–V
S
Figure 71. ADC Driver
16-BIT ADC DRIVER
Table 6. ADC Driver Performance, fC = 20 kHz,
VOUT = 2.24 V p-p
Ultralow noise and distortion performance make the AD8099
an ideal ADC driver. Even though the AD8099 is not unity gain
stable, it can be configured to produce a net gain of +1
amplifier, as shown in Figure 71. This is achieved by combining
a gain of +2 and a gain of –1 for a net gain of +1. The input
range of the ADC is 0 V to 2.5 V.
Parameter
Measurement (dB)
Second Harmonic Distortion
Third Harmonic Distortion
THD
SFDR
SNR
–111.4
–103.2
–101.4
102.2
88.1
Table 6 shows the performance data of the AD8099 and the
Analog Devices AD7667 a 1 MSPS 16-bit ADC.
Rev. B | Page 22 of 28
AD8099
Grounding
CIRCUIT CONSIDERATIONS
When possible, ground and power planes should be used.
Ground and power planes reduce the resistance and inductance
of the power supply feeds and ground returns. If multiple planes
are used, they should be “stitched” together with multiple vias.
The returns for the input, output terminations, bypass
capacitors, and RG should all be kept as close to the AD8099 as
possible. Ground vias should be placed at the very end of the
component mounting pad to provide a solid ground return. The
output load ground and the bypass capacitor grounds should be
returned to a common point on the ground plane to minimize
parasitic inductance and improve distortion performance. The
AD8099 packages feature an exposed paddle. For optimum
performance, solder this paddle to ground. For more
information on PCB layout and design considerations, refer to
section 7-2 of the 2002 Analog Devices Op Amp Applications
book.
Optimizing the performance of the AD8099 requires attention
to detail in layout and signal routing of the board. Power supply
bypassing, parasitic capacitance, and component selection all
contribute to the overall performance of the amplifier. The
AD8099 features an exposed paddle on the backs of both the
CSP and SOIC packages. The exposed paddle provides a low
thermal resistive path to the ground plane. For best
performance, solder the exposed paddle to the ground plane.
PCB Layout
The compensation network is determined by the amplifier gain
requirements. For lower gains, the layout and component
placement are more critical. For higher gains, there are fewer
compensation components, which results in a less complex
layout. With diligent consideration to layout, grounding, and
component placement, the AD8099 evaluation boards have
been optimized for peak performance. These are the same
evaluation boards that are available to customers; see Table 7 for
ordering information. The noninverting evaluation board art-
work for SOIC and CSP layouts are shown in Figure 72 and
Figure 73. Incorporating the layout information shown in
Figure 72 and Figure 73 into new designs is highly recom-
mended and helps to ensure optimal circuit performance. The
concepts of layout, grounding, and component placement,
llustrated in Figure 72 and Figure 73,also apply to inverting
configurations. For scale, the boards are 2” × 2”.
Power Supply Bypassing
The AD8099 power supply bypassing has been optimized for
each gain configuration as shown in Figure 60 through
Figure 66 in the Circuit Configurations section. The values
shown should be used when possible. Bypassing is critical for
stability, frequency response, distortion, and PSRR
performance. The 0.1 µF capacitors shown in Figure 60 through
Figure 66 should be as close to the supply pins of the AD8099 as
possible and the electrolytic capacitors beside them.
Component Selection
Parasitics
Smaller components less than 1206 SMT case size, offer smaller
mounting pads, which have less parasitics and allow for a more
compact layout. It is critical for optimum performance that high
quality, tight tolerance (where critical), and low drift compo-
nents be used. For example, tight tolerance and low drift is
critical in the selection of the feedback capacitor used in
Figure 60. The feedback compensation capacitor in Figure 60 is
1.5pF. This capacitor should be specified with NPO material.
NPO material typically has a ±30 ppm/°C change over –55°C to
+125°C temperature range. For a 100°C change, this would
result in a 4.5 fF change in capacitance, compared to an X7R
material, which would result in a 0.23 pF change, a 15% change
from the nominal value. This could introduce excessive
peaking, as shown in Figure 68, CF vs. Frequency Response.
The area surrounding the compensation pin is very sensitive to
parasitic capacitance. To realize the full gain bandwidth product
of the AD8099, there should be no trace connected to or within
close proximity of the external compensation pin for the lowest
possible capacitance. When compensation is required, the
traces to the compensation pin, the negative supply, and the
interconnect between components (i.e. CC, C1, and RC in Figure
59) should be made as wide as possible to minimize inductance.
All ground and power planes under the pins of the AD8099
should be cleared of copper to prevent parasitic capacitance
between the input and output pins to ground. A single mount-
ing pad on a SOIC footprint can add as much as 0.2 pF of
capacitance to ground as a result of not clearing the ground or
power plane under the AD8099 pins. Parasitic capacitance can
cause peaking and instability, and should be minimized to
ensure proper operation.
DESIGN TOOLS AND TECHNICAL SUPPORT
Analog Devices is committed to the design process by providing
technical support and online design tools. ADI offers technical
support via free evaluation boards, sample ICs, SPICE models,
interactive evaluation tools, application notes, phone and email
support—all available at www.analog.com.
The new pinout of the AD8099 reduces the distance between
the output and the inverting input of the amplifier. This helps to
minimize the parasitic inductance and capacitance of the
feedback path, which, in turn, reduces ringing and second
harmonic distortion.
Rev. B | Page 23 of 28
AD8099
Figure 72. SOIC Evaluation Board Artwork
Figure 73. CSP Evaluation Board Artwork
Evaluation Boards
There are four different evaluation boards available, as shown in Table 7, and an Application Note, AN-720, that explains the use of the
evaluation boards.
Table 7. Evaluation Board Selection Guide
Package Type
Board Configuration
Inverting
Noninverting
CSP
SOIC
EVAL-ADOPAMP-1CSP-I
EVAL-ADOPAMP-1CSP-N
EVAL-ADOPAMP-1R-IN
EVAL-ADOPAMP-1R-NI
Rev. B | Page 24 of 28
AD8099
OUTLINE DIMENSIONS
5.00 (0.197)
4.90 (0.193)
4.80 (0.189)
BOTTOM VIEW
(PINS UP)
2.29 (0.092)
4.00 (0.157)
3.90 (0.154)
3.80 (0.150)
8
5
2.29 (0.092)
6.20 (0.244)
6.00 (0.236)
5.80 (0.228)
TOP VIEW
1
4
1.27 (0.05)
BSC
0.50 (0.020)
0.25 (0.010)
× 45°
1.75 (0.069)
1.35 (0.053)
0.25 (0.0098)
0.10 (0.0039)
8°
0°
1.27 (0.050)
0.40 (0.016)
0.51 (0.020)
0.31 (0.012)
0.25 (0.0098)
0.17 (0.0068)
COPLANARITY
0.10
SEATING
PLANE
COMPLIANT TO JEDEC STANDARDS MS-012
CONTROLLING DIMENSIONS ARE IN MILLIMETERS; INCH DIMENSIONS
(IN PARENTHESES) ARE ROUNDED-OFF MILLIMETER EQUIVALENTS FOR
REFERENCE ONLY AND ARE NOT APPROPRIATE FOR USE IN DESIGN
Figure 74. 8-Lead Standard Small Outline Package [SOIC-ED]
(RD-8-1)
0.50
0.40
0.30
3.00
BSC SQ
0.60 MAX
8
PIN 1
INDICATOR
0.45
1
PIN 1
INDICATOR
1.90
1.75
1.60
2.75
BSC SQ
TOP
VIEW
1.50
REF
BOTTOM
VIEW
0.50
BSC
4
5
0.25
MIN
1.60
1.45
1.30
0.80 MAX
0.65TYP
0.90
0.85
0.80
12° MAX
0.05 MAX
0.02 NOM
SEATING
PLANE
0.30
0.23
0.18
0.20 REF
Figure 75. 8-Lead Plastic Surface-Mount Package [CSP]
(CP-8)
Dimensions shown in millimeters
Rev. B | Page 25 of 28
AD8099
ORDERING GUIDE
Model
Minimum Ordering Quantity
Temperature Range Package Description Branding Package Option
AD8099ARD
1
–40°C to +125°C
–40°C to +125°C
–40°C to +125°C
–40°C to +125°C
–40°C to +125°C
–40°C to +125°C
–40°C to +125°C
–40°C to +125°C
–40°C to +125°C
–40°C to +125°C
–40°C to +125°C
–40°C to +125°C
8-Lead SOIC-ED
8-Lead SOIC-ED
8-Lead SOIC-ED
8-Lead SOIC-ED
8-Lead SOIC-ED
8-Lead SOIC-ED
8-Lead CSP
8-Lead CSP
8-Lead CSP
8-Lead CSP
8-Lead CSP
RD-8-1
RD-8-1
RD-8-1
RD-8-1
RD-8-1
RD-8-1
CP-8
CP-8
CP-8
CP-8
CP-8
AD8099ARD-REEL
AD8099ARD-REEL7
AD8099ARDZ1
AD8099ARDZ-REEL1
AD8099ARDZ-REEL71 1,000
AD8099ACP-R2
AD8099ACP-REEL
AD8099ACP-REEL7
AD8099ACPZ-R21
AD8099ACPZ-REEL1
AD8099ACPZ-REEL71
2,500
1,000
1
2,500
250
HDB
HDB
HDB
HDB
HDB
HDB
5,000
1,500
250
5,000
1,500
8-Lead CSP
CP-8
1 Z = Pb free
Rev. B | Page 26 of 28
AD8099
NOTES
Rev. B | Page 27 of 28
AD8099
NOTES
©
2004 Analog Devices, Inc. All rights reserved. Trademarks and
registered trademarks are the property of their respective owners.
D04511–0–6/04(B)
Rev. B | Page 28 of 28
AD8099ARD-REEL7 CAD模型
引脚图
封装焊盘图
AD8099ARD-REEL7 替代型号
| 型号 | 制造商 | 描述 | 替代类型 | 文档 |
| AD8099ARDZ-REEL | ADI | Ultralow Distortion, High Speed 0.95 nV/Hz Voltage Noise Op Amp | 完全替代 |
|
| AD8099ARDZ | ADI | Ultralow Distortion, High Speed 0.95 nV/Hz Voltage Noise Op Amp | 类似代替 |
|
AD8099ARD-REEL7 相关器件
| 型号 | 制造商 | 描述 | 价格 | 文档 |
| AD8099ARDI-EBZ | ADI | Ultralow Distortion, High Speed 0.95 nV/ïHz Voltage Noise Op Amp | 获取价格 |
|
| AD8099ARDN-EBZ | ADI | Ultralow Distortion, High Speed 0.95 nV/ïHz Voltage Noise Op Amp | 获取价格 |
|
| AD8099ARDZ | ADI | Ultralow Distortion, High Speed 0.95 nV/Hz Voltage Noise Op Amp | 获取价格 |
|
| AD8099ARDZ-REEL | ADI | Ultralow Distortion, High Speed 0.95 nV/Hz Voltage Noise Op Amp | 获取价格 |
|
| AD8099ARDZ-REEL7 | ADI | Ultralow Distortion, High Speed 0.95 nV/Hz Voltage Noise Op Amp | 获取价格 |
|
| AD8099_13 | ADI | Ultralow Distortion, High Speed 0.95 nV/ïHz Voltage Noise Op Amp | 获取价格 |
|
| AD809BR | ADI | 155.52 MHz Frequency Synthesizer | 获取价格 |
|
| AD809BR | ROCHESTER | 155.52 MHz, OTHER CLOCK GENERATOR, PDSO16, 0.150 INCH, SOIC-16 | 获取价格 |
|
| AD809BR-REEL | ADI | IC 155.52 MHz, OTHER CLOCK GENERATOR, PDSO16, 0.150 INCH, SOIC-16, Clock Generator | 获取价格 |
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| AD809BR-REEL7 | ADI | 155.52 MHz Frequency Synthesizer | 获取价格 |
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