AD9861BCPZRL-80 [ADI]
Transceiver for Broadband Applications;
| 型号： | AD9861BCPZRL-80 |
| 厂家： | 
ADI |
| 描述： | Transceiver for Broadband Applications |
| 文件： | 总52页 (文件大小：977K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
Mixed-Signal Front-End (MxFE™) Baseband
Transceiver for Broadband Applications
Data Sheet
AD9861
FEATURES
FUNCTIONAL BLOCK DIAGRAM
Receive path includes dual 10-bit analog-to-digital converters
with internal or external reference, 50 MSPS and 80 MSPS
versions
Transmit path includes dual 10-bit, 200 MSPS digital-to-analog
converters with 1×, 2×, or 4× interpolation and programmable
gain control
Internal clock distribution block includes a programmable phase-
locked loop and timing generation circuitry, allowing single-
reference clock operation
20-pin flexible I/O data interface allows various interleaved or
noninterleaved data transfers in half-duplex mode and
interleaved data transfers in full-duplex mode
Configurable through register programmability or optionally
limited programmability through mode pins
Independent Rx and Tx power-down control pins
64-lead LFCSP package (9 mm × 9 mm footprint)
3 configurable auxiliary converter pins
VIN+A
ADC
DATA
MUX
AND
Rx DATA
VIN–A
VIN+B
LATCH
ADC
VIN–B
I/O
INTERFACE
CONTROL
I/O
INTERFACE
CONFIGURATION
BLOCK
FLEXIBLE
I/O BUS
[0:19]
LOW-PASS
INTERPOLATION
FILTER
IOUT+A
DATA
LATCH
AND
DAC
DAC
IOUT–A
IOUT+B
Tx DATA
DEMUX
IOUT–B
AUX
ADC
AUX
DAC
ADC CLOCK
CLKIN
AUX
DAC
APPLICATIONS
DAC CLOCK
PLL
Broadband access
AUX
ADC
Broadband LAN
Communications (modems)
AD9861
AUX
DAC
03606-0-001
Figure 1.
GENERAL DESCRIPTION
The AD9861 is a member of the MxFE family—a group of integrated
converters for the communications market. The AD9861 integrates
dual 10-bit analog-to-digital converters (ADC) and dual 10-bit
digital-to-analog converters (TxDAC®). Two speed grades are
available, -50 and -80. The -50 is optimized for ADC sampling of 50
MSPS and less, while the -80 is optimized for ADC sample rates
between 50 MSPS and 80 MSPS. The dual TxDACs operate at speeds
up to 200 MHz and include a bypassable 2× or 4× interpolation
filter. Three auxiliary converters are also available to provide
required system level control voltages or to monitor system signals.
The AD9861 is optimized for high performance, low power, small
form factor, and to provide a cost-effective solution for the
broadband communication market.
In half-duplex systems, the interface supports 20-bit parallel
transfers or 10-bit interleaved transfers. In full-duplex systems,
the interface supports an interleaved 10-bit ADC bus and an
interleaved 10-bit TxDAC bus. The flexible I/O bus reduces pin
count and, therefore, reduces the required package size on the
AD9861 and the device to which it connects.
The AD9861 can use either mode pins or a serial program-
mable interface (SPI) to configure the interface bus, operate the
ADC in a low power mode, configure the TxDAC interpolation
rate, and control ADC and TxDAC power-down. The SPI
provides more programmable options for both the TxDAC path
(for example, coarse and fine gain control and offset control for
channel matching) and the ADC path (for example, the internal
duty cycle stabilizer, and twos complement data format).
The AD9861 uses a single input clock pin (CLKIN) to generate all
system clocks. The ADC and TxDAC clocks are generated within a
timing generation block that provides user programmable options
such as divide circuits, PLL multipliers, and switches.
The AD9861 is packaged in a 64-lead LFCSP (low profile, fine
pitched, chip scale package). The 64-lead LFCSP footprint is
only 9 mm × 9 mm, and is less than 0.9 mm high, fitting into
tightly spaced applications such as PCMCIA cards.
A flexible, bidirectional 20-bit I/O bus accommodates a variety of
custom digital back ends or open market DSPs.
Rev. A
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Tel: 781.329.4700 ©2003–2017 Analog Devices, Inc. All rights reserved.
Technical Support
www.analog.com
AD9861* PRODUCT PAGE QUICK LINKS
Last Content Update: 06/30/2017
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DESIGN RESOURCES
• AD9861 Material Declaration
• PCN-PDN Information
• Quality And Reliability
• Symbols and Footprints
EVALUATION KITS
• AD9861/AD9863 Evaluation Tools
DOCUMENTATION
Application Notes
DISCUSSIONS
View all AD9861 EngineerZone Discussions.
• AN-928: Understanding High Speed DAC Testing and
Evaluation
SAMPLE AND BUY
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Data Sheet
• AD9861: Mixed-Signal Front-End (MxFE™) Processor For
Broadband Applications Data Sheet
TECHNICAL SUPPORT
Submit a technical question or find your regional support
number.
TOOLS AND SIMULATIONS
• AD9861 IBIS Models
DOCUMENT FEEDBACK
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REFERENCE MATERIALS
Informational
• Advantiv™ Advanced TV Solutions
Technical Articles
• MS-2210: Designing Power Supplies for High Speed ADC
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AD9861
Data Sheet
TABLE OF CONTENTS
Features .......................................................................................................1
Typical Performance Characteristics.................................................... 10
Terminology............................................................................................. 21
Theory of Operation............................................................................... 22
System Block........................................................................................ 22
Rx Path Block ...................................................................................... 22
Tx Path Block ...................................................................................... 24
Auxiliary Converters .......................................................................... 27
Digital Block ........................................................................................ 30
Programmable Registers .................................................................... 42
Clock Distribution Block................................................................... 45
Outline Dimensions................................................................................ 49
Ordering Guide ................................................................................... 49
Applications................................................................................................1
Functional Block Diagram .......................................................................1
General Description..................................................................................1
TABLE OF CONTENTS...........................................................................2
Tx Path Specifications...............................................................................3
Rx Path Specifications...............................................................................4
Power Specifications..................................................................................5
Digital Specifications.................................................................................5
Timing Specifications................................................................................6
Absolute Maximum Ratings.....................................................................7
ESD Caution...........................................................................................7
Pin Configuration and Pin Function Descriptions...............................8
REVISION HISTORY
4/2017—Rev. 0 to Rev. A
Changes to Figure 3 and Table 8..................................................... 8
Updated Outline Dimensions....................................................... 44
Changes to Ordering Guide .......................................................... 44
11/2003—Revision 0: Initial Version
Rev. A | Page 2 of 51
Data Sheet
AD9861
TX PATH SPECIFICATIONS
Table 1. AD9861-50 and AD9861-80
F
DAC = 200 MSPS; 4× interpolation; RSET = 4.02 kΩ; differential load resistance of 100 Ω1; TxPGA = 20 dB, AVDD = DVDD = 3.3 V,
unless otherwise noted
Parameter
Temp
Test Level
Min
Typ
Max
Unit
Tx PATH GENERAL
Resolution
Full
Full
Full
Full
25°C
Full
Full
Full
25°C
Full
Full
Full
IV
IV
IV
V
IV
IV
V
V
V
IV
V
V
10
Bits
MHz
mA
Maximum DAC Update Rate
Maximum Full-Scale Output Current
Full-Scale Error
Gain Mismatch Error
Offset Mismatch Error
Reference Voltage
200
20
1%
–3.5
–0.1
+3.5
+0.1
% FS
% FS
V
pF
dBc/Hz
V
1.23
5
–115
Output Capacitance
Phase Noise (1 kHz Offset, 6 MHz Tone)
Output Voltage Compliance Range
TxPGA Gain Range
–1.0
+1.0
20
0.10
dB
dB
TxPGA Step Size
Tx PATH DYNAMIC PERFORMANCE
(IOUTFS = 20 mA; FOUT = 1 MHz)
SNR
SINAD
THD
Full
Full
Full
Full
Full
IV
IV
IV
IV
IV
60.2
59.7
60.8
60.7
−77.5
76.0
81.0
dB
dB
dBc
dBc
dBc
−65.8
SFDR, Wideband (DC to Nyquist)
64.6
72.5
SFDR, Narrowband (1 MHz Window)
1 See Figure 2 for description of the TxDAC termination scheme.
TxDAC
50Ω
50Ω
03606-0-030
Figure 2. Diagram Showing Termination of 100 Ω Differential
Load for Some TxDAC Measurements
Rev. A | Page 3 of 51
AD9861
Data Sheet
Rx PATH SPECIFICATIONS
Table 2. AD9861-50 and AD9861-80
F
ADC = 50 MSPS for the AD9861-50, 80 MSPS for the AD9861-80; internal reference; differential analog inputs,
ADC_AVDD = DVDD = 3.3V, unless otherwise noted
Parameter
Temp
Test Level
Min
Typ
Max
Unit
Rx PATH GENERAL
Resolution
Maximum ADC Sample Rate
Gain Mismatch Error
Full
Full
Full
Full
Full
Full
Full
Full
Full
Full
V
IV
V
V
V
IV
V
V
V
V
10
Bits
MSPS
% FS
50/80
±0.2
±0.1
1.0
±6
2
5
30
2
Offset Mismatch Error
% FS
Reference Voltage
V
mV
Reference Voltage (REFT–REFB) Error
Input Resistance (Differential)
Input Capacitance
–30
+30
kΩ
pF
Input Bandwidth
MHz
V p-p differential
Differential Analog Input Voltage Range
Rx PATH DC ACCURACY
Integral Nonlinearity (INL)
Differential Nonlinearity (DNL)
Aperature Delay
25°C
25°C
25°C
25°C
25°C
V
V
V
V
V
LSB
LSB
ns
ps rms
uV
±0.75
±0.75
2.0
1.2
450
Aperature Uncertainty (Jitter)
Input Referred Noise
AD9861-50 Rx PATH DYNAMIC PERFORMANCE
(VIN = –0.5 dBFS; FIN = 10 MHz)
SNR
Full
Full
25°C
Full
Full
Full
IV
IV
IV
IV
IV
V
55.5
55.6
58.5
60
60
60
−71.5
73.5
80
dBc
dBc
dBc
dBc
dBc
dB
SINAD
SINAD
THD (Second to Ninth Harmonics)
SFDR, Wideband (DC to Nyquist)
Crosstalk between ADC Inputs
−64.6
65.7
AD9861-80 Rx PATH DYNAMIC PERFORMANCE
(VIN = –0.5 dBFS; FIN = 10 MHz)
SNR
Full
Full
Full
Full
Full
IV
IV
IV
IV
V
55.4
52.7
59.5
59.0
−67
67
dBc
dBc
dBc
dBc
dB
SINAD
THD (Second to Ninth Harmonics)
SFDR, Wideband (DC to Nyquist)
Crosstalk between ADC Inputs
80
Rev. A | Page 4 of 51
Data Sheet
AD9861
POWER SPECIFICATIONS
Table 3. AD9861-50 and AD9861-80
Analog and digital supplies = 3.3 V; FCLKIN = 50 MHz; PLL 4× setting; normal timing mode
Parameter
Temp
Test Level
Min
Typ
Max
Unit
POWER SUPPLY RANGE
Analog Supply Voltage (AVDD)
Digital Supply Voltage (DVDD)
Driver Supply Voltage (DRVDD)
ANALOG SUPPLY CURRENTS
TxPath (20 mA Full-Scale Outputs)
TxPath (2 mA Full-Scale Outputs)
Rx Path (-80, at 80 MSPS)
Full
Full
Full
IV
IV
IV
2.7
2.7
2.7
3.6
3.6
3.6
V
V
V
Full
Full
Full
Full
Full
Full
Full
Full
Full
Full
Full
V
V
V
V
V
V
V
V
V
V
V
70
20
165
82
35
103
69
28
2
mA
mA
mA
mA
mA
mA
mA
mA
mA
mA
mA
RxPath (-80, at 40 MSPS, Low Power Mode)
RxPath (-80, at 20 MSPS, Ultralow Power Mode)
Rx Path (-50, at 50 MSPS)
RxPath (-50, at 50 MSPS, Low Power Mode)
RxPath (-50, at 16 MSPS, Ultralow Power Mode)
TxPath, Power-Down Mode
RxPath, Power-Down Mode
PLL
5
12
DIGITAL SUPPLY CURRENTS
TxPath, 1× Interpolation,
Full
Full
Full
Full
V
V
V
V
20
50
80
15
mA
mA
mA
mA
50 MSPS DAC Update for Both DACs,
Half-Duplex 24 Mode
TxPath, 2× Interpolation,
100 MSPS DAC Update for Both DACs,
Half-Duplex 24 Mode
TxPath, 4× Interpolation,
200 MSPS DAC Update for Both DACs,
Half-Duplex 24 Mode
RxPath Digital, Half-Duplex 24 Mode
DIGITAL SPECIFICATIONS
Table 4. AD9861-50 and AD9861-80
Parameter
Temp
Test Level
Min
Typ
Max
Unit
LOGIC LEVELS
Input Logic High Voltage, VIH
Input Logic Low Voltage, VIL
Output Logic High Voltage, VOH (1 mA Load)
Output Logic Low Voltage, VOL (1 mA Load)
DIGITAL PIN
Full
Full
Full
Full
IV
IV
IV
IV
DRVDD – 0.7
DRVDD – 0.6
V
V
V
V
0.4
0.4
12
Input Leakage Current
Input Capacitance
Minimum RESET Low Pulse Width
Digital Output Rise/Fall Time
Full
Full
Full
Full
IV
IV
IV
IV
µA
pF
3
5
2.8
Input Clock Cycles
ns
4
Rev. A | Page 5 of 51
AD9861
Data Sheet
TIMING SPECIFICATIONS
Table 5. AD9861-50 and AD9861-80
Parameter
Temp
Test Level
Min
Typ
Max
Unit
INPUT CLOCK
CLKIN Clock Rate (PLL Bypassed)
PLL Input Frequency
PLL Ouput Frequency
TxPATH DATA
Full
Full
Full
IV
IV
IV
1
16
32
200
200
350
MHz
MHz
MHz
Setup Time (HD20 Mode, Time Required Before Data Latching
Edge)
Full
V
V
5
ns (see Clock
Distribution Block
section)
ns (see Clock
Distribution Block
section)
Hold Time (HD20 Mode, Time Required After Data Latching Edge) Full
–1.5
Latency 1× Interpolation (data in until peak output response)
Latency 2× Interpolation (data in until peak output response)
Latency 4× Interpolation (data in until peak output response)
Full
Full
Full
V
V
V
7
35
83
DAC Clock Cycles
DAC Clock Cycles
DAC Clock Cycles
RxPATH DATA
Output Delay (HD20 Mode, tOD
)
Full
Full
V
V
–1.5
5
ns (see Clock
Distribution Block
section)
Latency
ADC Clock Cycles
Table 6. Explanation of Test Levels
Level
Description
I
100% production tested.
II
100% production tested at 25°C and guaranteed by design and characterization at specified temperatures.
Sample tested only.
Parameter is guaranteed by design and characterization testing.
Parameter is a typical value only.
III
IV
V
VI
100% production tested at 25°C and guaranteed by design and characterization for industrial temperature range.
Rev. A | Page 6 of 51
Data Sheet
AD9861
ABSOLUTE MAXIMUM RATINGS
Table 7.
Thermal Resistance
64-lead LFCSP (4-layer board):
Parameter
Rating
θJA = 24.2 (paddle soldered to ground plan, 0 LPM Air)
θJA = 30.8 (paddle not soldered to ground plan, 0 LPM Air)
Electrical
AVDD Voltage
3.9 V max
Stresses at or above those listed under Absolute Maximum Ratings
may cause permanent damage to the product. This is a stress
rating only; functional operation of the product at these or any
other conditions above those indicated in the operational section
of this
DRVDD Voltage
Analog Input Voltage
Digital Input Voltage
Digital Output Current
Environmental
3.9 V max
–0.3 V to AVDD + 0.3 V
–0.3 V to DVDD – 0.3 V
5 mA max
Operating Temperature Range
(Ambient)
ESD CAUTION
–40°C to +85°C
Maximum Junction Temperature
150°C
300°C
Lead Temperature (Soldering, 10 sec)
Storage Temperature Range
(Ambient)
–65°C to +150°C
Rev. A | Page 7 of 51
AD9861
Data Sheet
PIN CONFIGURATION AND PIN FUNCTION DESCRIPTIONS
CLKIN
SPI_DIO
SPI_CLK
SPI_SDO/AUX_SPI_SDO
ADC_LO_PWR/AUX_SPI_CS
48
47
46
45
44
43
42
41
40
39
38
37
36
35
34
33
1
2
3
4
5
6
7
8
9
AUXADC_REF
RESET
AUX_DACC/AUX_ADCB
L0
L1
L2
L3
L4
L5
L6
DVDD
DVSS
AVDD
IOUT–A
IOUT+A
AGND
REFIO
FSADJ 12
AGND 13
AD9861
TOP VIEW
(Not to Scale)
10
11
L7
L8
L9
IOUT+B
IOUT–B 15
AVDD 16
14
AUX_SPI_CLK
IFACE1
NOTESꢀ
1. EXPOSED PAD. THE EXPOSED PAD MUST BE SECURELY CONNECTED TO THE GROUND PLANE.
Figure 3. Pin Configuration
Table 8. Pin Function Descriptions
Pin No.
Name1
Description2, 3
1
SPI_DIO
SPI: Serial Port Data Input.
(Interp1)
No SPI: Tx Interpolation Pin, MSB.
2
3
SPI_CLK
(Interp0)
SPI: Serial Port Shift Clock.
No SPI: Tx Interpolation Pin, LSB.
SPI: 4-Wire Serial Port Data Output/Data Output Pin for AuxSPI.
No SPI: Configures Full-Duplex or Half-Duplex Mode.
SPI_SDO/AUXSPI_SDO
(FD/HD)
4
5, 31
ADC_LO_PWR/AUX_SPI_CS
DVDD
ADC Low Power Mode Enable. Defined at power-up. CS for AuxSPI.
Digital Supply.
6, 32
DVSS
Digital Ground.
7, 16, 50, 51, 61
AVDD
Analog Supply.
8, 9
IOUT–A, IOUT+A
AGND, AVSS
REFIO
DAC A Differential Output.
Analog Ground.
Tx DAC Band Gap Reference Decoupling Pin.
Tx DAC Full-Scale Adjust Pin.
10, 13, 49, 53, 59
11
12
FSADJ
14, 15
17
IOUT+B, IOUT−B
IFACE2
DAC B Differential Output.
SPI: Buffered CLKIN. Can be configured as system clock output.
(10/20)
No SPI: For FD: Buffered CLKIN; For HD20 or HD10 : 10/20 Configuration Pin.
Clock Output.
Upper Data Bit 9 to Upper Data Bit 0.
Configurable as either AuxADC_A2 or AuxDAC_A.
Configurable as either AuxADC_A1 or AuxDAC_B.
18
19–28
29
IFACE3
U9–U0
AUX1
30
AUX2
33
IFACE1
SPI: For FD: TxSYNC; For HD20, HD10, or Clone: Tx/
No SPI: FD >> TxSYNC; HD20 or HD10: Tx/Rx.
CLK for AuxSPI.
Rx
.
34
35–44
AUX_SPI_CLK
L9–L0
Lower Data Bit 9 to Lower Data Bit 0.
Rev. A | Page 8 of 51
Data Sheet
AD9861
Pin No.
45
46
Name1
Description2, 3
AUX3
RESET
Configurable as either AuxADC_B or AuxDAC_C.
Chip Reset When Low.
47
48
AUX_ADC_REF
CLKIN
Decoupling for AuxADC On-Chip Reference.
Clock Input.
52
REFB
ADC Bottom Reference.
54, 55
56
VIN+B, VIN−B
VREF
ADC B Differential Input.
ADC Band Gap Reference.
57, 58
60
VIN−A, VIN+A
REFT
ADC A Differential Input.
ADC Top Reference.
62
63
64
RxPwrDwn
TxPwrDwn
SPI_CS
Rx Analog Power-Down Control.
Tx Analog Power-Down Control.
SPI: Serial Port Chip Select. At power-up or reset, this must be high.
No SPI: Tie low to disable SPI and use mode pins. This pin must be tied low.
EPAD
Exposed Pad. The exposed pad must be securely connected to the ground plane.
1 Underlined pin names and descriptions apply when the device is configured without a serial port interface, referred to as no SPI mode.
2 Pin function depends if the serial port is used to configure the AD9861 (called SPI mode) or if mode pins are used to configure the AD9861 (called No SPI mode). The
differences are indicated by the SPI and No SPI labels in the description column.
3 Some pin descriptions depend on the interface configuration, full-duplex (FD), half-duplex interleaved data (HD10), half-duplex parallel data (HD20), and a half-duplex
interface similar to the AD9860 and AD9862 data interface called clone mode (Clone). Clone mode requires a serial port interface.
Rev. A | Page 9 of 51
AD9861
Data Sheet
TYPICAL PERFORMANCE CHARACTERISTICS
0
–10
–20
–30
–40
–50
–60
–70
–80
–90
–100
–110
0
–10
–20
–30
–40
–50
–60
–70
–80
–90
–100
–110
0
5
10
15
20
25
0
5
10
15
20
25
FREQUENCY (MHz)
FREQUENCY (MHz)
Figure 4. AD9861-50 Rx Path Single-Tone FFT of Rx Channel B Path
Digitizing 2 MHz Tone
Figure 7. AD9861-50 Rx Path Dual-Tone FFT of Rx Channel A Path
Digitizing 1 MHz and 2 MHz Tones
0
–10
–20
–30
–40
–50
–60
–70
–80
–90
–100
–110
0
–10
–20
–30
–40
–50
–60
–70
–80
–90
–100
–110
0
5
10
15
20
25
0
5
10
15
20
25
FREQUENCY (MHz)
FREQUENCY (MHz)
Figure 5. AD9861-50 Rx Path Single-Tone FFT of Rx Channel B Path
Digitizing 5 MHz Tone
Figure 8. AD9861-50 Rx Path Dual-Tone FFT of Rx Channel A Path
Digitizing 5 MHz and 8 MHz Tones
0
–10
–20
–30
–40
–50
–60
–70
–80
–90
–100
–110
0
–10
–20
–30
–40
–50
–60
–70
–80
–90
–100
–110
0
5
10
15
20
25
0
5
10
15
20
25
FREQUENCY (MHz)
FREQUENCY (MHz)
Figure 9. AD9861-50 Rx Path Dual-Tone FFT of Rx Channel A Path
Digitizing 20 MHz and 25 MHz Tones
Figure 6. AD9861-50 Rx Path Single-Tone FFT of Rx Channel B Path
Digitizing 24 MHz Tone
Rev. A | Page 10 of 51
Data Sheet
AD9861
0
–10
–20
–30
–40
–50
–60
–70
–80
–90
–100
0
–10
–20
–30
–40
–50
–60
–70
–80
–90
–100
–110
–110
0
5
10
15
20
25
0
5
10
15
20
25
FREQUENCY (MHz)
FREQUENCY (MHz)
Figure 10. AD9861-50 Rx Path Single-Tone FFT of Rx Channel B Path
Digitizing 76 MHz Tone
Figure 13. AD9861-50 Rx Path Dual-Tone FFT of Rx Channel A Path
Digitizing 70 MHz and 72 MHz Tones
62
62
59
56
53
50
10.0
9.8
9.6
9.4
9.2
9.0
8.8
8.6
8.4
8.2
8.0
NORMAL POWER @ 50MSPS
NORMAL POWER @ 50MSPS
LOW POWER ADC @ 25MSPS
LOW POWER ADC @ 25MSPS
59
56
ULTRALOW POWER ADC
ULTRALOW POWER ADC
@ 16MSPS
@ 16MSPS
53
50
0
5
10
15
20
25
0
5
10
15
20
25
INPUT FREQUENCY (MHz)
INPUT FREQUENCY (MHz)
Figure 11. AD9861-50 Rx Path at 50 MSPS, 10 MHz Input Tone
SNR Performance vs. Input Frequency
Figure 14. AD9861-50 Rx Path at 50 MSPS, 10 MHz Input Tone
SINAD Performance vs. Input Frequency
–50
80
LOW POWER ADC @ 25MSPS
–55
75
NORMAL POWER @ 50MSPS
70
–60
ULTRALOW POWER ADC
@ 16MSPS
–65
65
60
NORMAL POWER @ 50MSPS
–70
–75
ULTRALOW POWER ADC
@ 16MSPS
55
LOW POWER ADC @ 25MSPS
–80
50
0
5
10
15
20
25
0
5
10
15
20
25
INPUT FREQUENCY (MHz)
INPUT FREQUENCY (MHz)
Figure 15. AD9861-50 Rx Path at 50 MSPS, 10 MHz Input Tone
THD Performance vs. Input Frequency
Figure 12. AD9861-50 Rx Path at 50 MSPS, 10 MHz Input Tone
SFDR Performance vs. Input Frequency
Rev. A | Page 11 of 51
AD9861
Data Sheet
70
60
50
40
30
20
10
90
80
70
60
50
40
30
20
–90
–80
–70
–60
–50
–40
–30
–20
SFDR
THD
IDEAL SNR
SNR
0
0
–5
–10
–15
–20
–25
–30
–35
–40
–45
0
–5
–10
–15
–20
–25
–30
–35
–40
INPUT AMPLITUDE (dBFS)
INPUT AMPLITUDE (dBFS)
Figure 16. AD9861-50 Rx Path at 50 MSPS, 10 MHz Input Tone
SNR Performance vs. Input Amplitude
Figure 19. AD9861-50 Rx Path at 50 MSPS, 10 MHz Input Tone
THD and SFDR Performance vs. Input Amplitude
62
62
61
60
59
58
57
56
10.0
9.9
9.8
9.7
9.6
9.5
9.4
9.3
9.2
9.1
9.0
AVE (–40C)
61
AVE (–40C)
AVE (+25C)
AVE (+25C)
60
AVE (+85C)
AVE (+85C)
59
58
57
56
2.7
3.0
3.3
3.6
2.7
3.0
3.3
3.6
ADC_AVDD VOLTAGE (V)
ADC_AVDD VOLTAGE (V)
Figure 17. AD9861-50 Rx Path at 50 MSPS, 10 MHz Input Tone
SNR Performance vs. ADC_AVDD and Temperature
Figure 20. AD9861-50 Rx Path at 50 MSPS, 10 MHz Input Tone
SINAD Performance vs. ADC_AVDD and Temperature
–70.0
–70.5
70
71
72
–71.0
AVE (+85C)
–71.5
–72.0
AVE (+85C)
73
AVE (+25C)
–72.5
74
AVE (+25C)
–73.0
–73.5
75
AVE (–40C)
76
77
78
AVE (–40C)
–74.0
–74.5
–75.0
3.6
3.3
3.0
2.7
3.6
3.3
3.0
2.7
INPUT AMPLITUDE (dBFS)
INPUT AMPLITUDE (dBFS)
Figure 18. AD9861-50 Rx Path Single-Tone THD Performance vs.
ADC_AVDD and Temperature
Figure 21. AD9861-50 Rx Path Single-Tone SFDR Performance vs.
ADC_AVDD and Temperature
Rev. A | Page 12 of 51
Data Sheet
AD9861
0
–10
–20
–30
–40
–50
–60
–70
–80
–90
–100
–110
0
–10
–20
–30
–40
–50
–60
–70
–80
–90
–100
–110
0
5
10
15
20
25
30
35
40
0
5
10
15
20
25
FREQUENCY (MHz)
FREQUENCY (MHz)
Figure 22. AD9861-80 Rx Path Single-Tone FFT of Rx Channel B Path
Digitizing 2 MHz Tone
Figure 25. AD9861-80 Rx Path Dual-Tone FFT of Rx Channel A Path
Digitizing 1 MHz and 2 MHz Tones
0
–10
–20
–30
–40
–50
–60
–70
–80
–90
–100
–110
0
–10
–20
–30
–40
–50
–60
–70
–80
–90
–100
–110
0
5
10
15
20
25
30
35
40
0
5
10
15
20
25
FREQUENCY (MHz)
FREQUENCY (MHz)
Figure 23. AD9861-80 Rx Path Single-Tone FFT of Rx Channel B Path
Digitizing 5 MHz Tone
Figure 26. AD9861-80 Rx Path Dual-Tone FFT of Rx Channel A Path
Digitizing 5 MHz and 8 MHz Tones
0
–10
–20
–30
–40
–50
–60
–70
–80
–90
–100
–110
0
–10
–20
–30
–40
–50
–60
–70
–80
–90
–100
–110
0
5
10
15
20
25
30
35
40
0
5
10
15
20
25
FREQUENCY (MHz)
FREQUENCY (MHz)
Figure 24. AD9861-80 Rx Path Single-Tone FFT of Rx Channel B Path
Digitizing 24 MHz Tone
Figure 27. AD9861-80 Rx Path Dual-Tone FFT of Rx Channel A Path
Digitizing 20 MHz and 25 MHz Tones
Rev. A | Page 13 of 51
AD9861
Data Sheet
62
62
59
56
53
50
10.0
9.8
LOW POWER ADC @ 40MSPS
ULTRALOW POWER ADC @ 16MSPS
LOW POWER ADC @ 40MSPS
NORMAL POWER @ 80MSPS
ULTRALOW POWER ADC @ 16MSPS
9.6
9.4
9.2
9.0
8.8
8.6
8.4
8.2
8.0
59
NORMAL POWER @ 80MSPS
56
53
50
0
5
10
15
20
25
30
0
5
10
15
20
25
30
INPUT FREQUENCY (MHz)
INPUT FREQUENCY (MHz)
Figure 28. AD9861-80 Rx Path at 80 MSPS, 10 MHz Input Tone
SNR Performance vs. Input Frequency and Power Setting
Figure 31. AD9861-80 Rx Path at 80 MSPS, 10 MHz Input Tone
SINAD Performance vs. Input Frequency and Power Setting
85
–50
–55
–60
LOW POWER ADC @ 40MSPS
80
ULTRALOW POWER
ADC @ 16MSPS
75
–65
LOW POWER ADC @ 40MSPS
70
–70
NORMAL POWER @ 80MSPS
65
–75
ULTRALOW POWER
ADC @ 16MSPS
NORMAL POWER @ 80MSPS
60
–80
0
5
10
15
20
25
0
5
10
15
20
25
INPUT FREQUENCY (MHz)
INPUT FREQUENCY (MHz)
Figure 29. AD9861-80 Rx Path at 80 MSPS, 10 MHz Input Tone
SFDR Performance vs. Input Frequency and Power Setting
Figure 32. AD9861-80 Rx Path at 80 MSPS, 10 MHz Input Tone
THD Performance vs. Input Frequency and Power Setting
70
60
50
–80
80
70
60
50
40
30
20
–70
–60
–50
–40
–30
–20
SFDR
40
IDEAL SNR
30
THD
20
SNR
10
0
0
–5
–10
–15
–20
–25
–30
–35
–40
–45
0
–5
–10
–15
–20
–25
–30
–35
–40
INPUT AMPLITUDE (dBFS)
INPUT AMPLITUDE (dBFS)
Figure 30. AD9861-80 Rx Path at 80 MSPS, 10 MHz Input Tone
SNR Performance vs. Input Amplitude
Figure 33. AD9861-80 Rx Path at 80 MSPS, 10 MHz Input Tone
THD Performance vs. Input Amplitude
Rev. A | Page 14 of 51
Data Sheet
AD9861
62
61
60
59
58
57
62
61
60
59
58
57
56
10.0
9.9
9.8
9.7
9.6
9.5
9.4
9.3
9.2
9.1
AVE (–40C)
AVE (+85C)
AVE (+25C)
AVE (+85C)
AVE (+25C)
AVE (–40C)
56
2.7
9.0
3.6
3.0
3.3
3.6
2.7
3.0
3.3
ADC_AVDD VOLTAGE (V)
ADC_AVDD VOLTAGE (V)
Figure 34. AD9861-80 Rx Path at 80 MSPS, 10 MHz Input Tone
SNR Performance vs. AVDD and Temperature
Figure 37. AD9861-80 Rx Path at 80 MSPS, 10 MHz Input Tone
SINAD Performance vs. AVDD and Temperature
70
69
65
AVE (+85C)
66
AVE (–40C)
68
67
68
AVE (+25C)
AVE (–40C)
67
66
65
64
63
62
61
60
AVE (+25C)
69
70
71
72
73
74
75
AVE (+85C)
2.7
3.0
3.3
3.6
2.7
3.0
3.3
3.6
ADC_AVDD VOLTAGE (V)
ADC_AVDD VOLTAGE (V)
Figure 35. AD9861-80 Rx Path at 80 MSPS, 10 MHz Input Tone
THD Performance vs. AVDD and Temperature
Figure 38. AD9861-80 Rx Path at 80 MSPS, 10 MHz Input Tone
SFDR Performance vs. AVDD and Temperature
120
180
160
NORM
NORM
100
140
120
80
100
LP
LP
60
80
60
40
40
ULP
20
0
ULP
20
0
0
10
20
F
30
(MHz)
40
50
0
10
20
30
40
(MHz)
50
60
70
80
F
CLK
CLK
Figure 36. AD9861-50 ADC_AVDD Current vs. Sampling Rate for
Different ADC Power Levels
Figure 39. AD9861-80 ADC_AVDD Current vs. ADC Sampling Rate for
Different ADC Power Levels
Rev. A | Page 15 of 51
AD9861
Data Sheet
0
–10
–20
–30
–40
–50
–60
–70
–80
–90
–100
0
–10
–20
–30
–40
–50
–60
–70
–80
–90
–100
–110
–110
0
0
5
10
15
20
25
5
10
15
20
25
FREQUENCY (MHz)
FREQUENCY (MHz)
Figure 43. AD9861 Tx Path 5 MHz Single-Tone Output FFT of Tx Path
with 20 mA Full-Scale Output into 33 Ω Differential Load
Figure 40. AD9861 Tx Path 1 MHz Single-Tone Output FFT of Tx Path
with 20 mA Full-Scale Output into 33 Ω Differential Load
0
–10
–20
–30
–40
–50
–60
–70
–80
–90
–100
–110
0
–10
–20
–30
–40
–50
–60
–70
–80
–90
–100
–110
0
5
10
15
20
25
0
5
10
15
20
25
FREQUENCY (MHz)
FREQUENCY (MHz)
Figure 44. AD9861 Tx Path 5 MHz Single-Tone Output FFT of Tx Path
with 20 mA Full-Scale Output into 60 Ω Differential Load
Figure 41. AD9861 Tx Path 1 MHz Single-Tone Output FFT of Tx Path
with 20 mA Full-Scale Output into 60 Ω Differential Load
0
–10
–20
–30
–40
–50
–60
–70
–80
–90
–100
–110
0
–10
–20
–30
–40
–50
–60
–70
–80
–90
–100
–110
0
5
10
15
20
25
0
5
10
15
20
25
FREQUENCY (MHz)
FREQUENCY (MHz)
Figure 45. AD9861 Tx Path 5 MHz Single-Tone Output FFT of Tx Path
with 2 mA Full-Scale Output into 600 Ω Differential Load
Figure 42. AD9861 Tx Path 1 MHz Single-Tone Output FFT of Tx Path
with 2 mA Full-Scale Output into 600 Ω Differential Load
Rev. A | Page 16 of 51
Data Sheet
AD9861
–50
–60
–70
–80
–90
–50
–60
–70
–80
–90
–100
0
–100
5
10
15
20
25
0
5
10
15
20
25
OUTPUT FREQUENCY (MHz)
OUTPUT FREQUENCY (MHz)
Figure 46. AD9861 Tx Path THD vs. Output Frequency of Tx Path with
20 mA Full-Scale Output into 60 Ω Differential Load
Figure 49. AD9861 Tx Path THD vs. Output Frequency of Tx Path
with 2 mA Full-Scale Output into 600 Ω Differential Load
62
61
60
59
58
57
56
62
61
60
59
58
57
56
0
5
10
15
20
25
0
5
10
15
20
25
OUTPUT FREQUENCY (MHz)
OUTPUT FREQUENCY (MHz)
Figure 47. AD9861 Tx Path SINAD vs. Output Frequency of Tx Path, with
20 mA Full-Scale Output into 60 Ω Differential Load
Figure 50. AD9861 Tx Path SINAD vs. Output Frequency of Tx Path, with
2 mA Full-Scale Output into 600 Ω Differential Load
–70
–75
–80
–85
–90
–95
–70
–75
–80
–85
–90
–95
0
5
10
15
20
25
0
5
10
15
20
25
OUTPUT FREQUENCY (MHz)
OUTPUT FREQUENCY (MHz)
Figure 48. AD9861 Tx Path Dual-Tone (0.5 MHz Spacing) IMD vs.
Output Frequency of Tx Path, with
Figure 51. AD9861 Tx Path Dual-Tone (0.5 MHz Spacing) IMD vs.
Output Frequency of Tx Path, with
20 mA Full-Scale Output into 60 Ω Differential Load
2 mA Full-Scale Output into 600 Ω Differential Load
Rev. A | Page 17 of 51
AD9861
Data Sheet
Figure 52 to Figure 57 use the same input data to the Tx path, a 64-carrier OFDM signal over a 20 MHz bandwidth, centered at 20 MHz. The
center two carriers are removed from the signal to observe the in-band intermodulation distortion (IMD) from the DAC output.
–30
–30
–40
–40
–50
–50
–60
–60
–70
–70
–80
–80
–90
–90
–100
–110
–120
–130
–100
–110
–120
–130
7.5
12.5
17.5
22.5
27.5
32.5
18.75
19.25
19.75
20.25
20.75
21.25
FREQUENCY (MHz)
FREQUENCY (MHz)
Figure 52. AD9861 Tx Path FFT, 64-Carrier (Center Two Carriers Removed)
OFDM Signal over 20 MHz Bandwidth, Centered at 20 MHz, with
20 mA Full-Scale Output into 60 Ω Differential Load
Figure 55. AD9861 Tx Path FFT, In-Band IMD Products of
OFDM Signal in Figure 52
–30
–40
–30
–40
–50
–50
–60
–60
–70
–70
–80
–80
–90
–90
–100
–110
–120
–130
–100
–110
–120
–130
7.5
8.0
8.5
9.0
9.5 10.0 10.5 11.0 11.5 12.0 12.5
FREQUENCY (MHz)
27.5 28.0 28.5 29.0 29.5 30.0 30.5 31.0 31.5 32.0 32.5
FREQUENCY (MHz)
Figure 53. AD9861 Tx Path FFT, Lower-Band IMD Products of
OFDM Signal in Figure 52
Figure 56. AD9861 Tx Path FFT, Upper-Band IMD Products of
OFDM Signal in Figure 52
–30
–40
–50
–60
–70
–80
–90
–30
–40
–50
–60
–70
–80
–90
–100
–100
–110
–120
–130
–110
–120
–130
0
10
20
30
40
50
60
70
80
0
10
20
30
40
50
60
70
80
FREQUENCY (MHz)
FREQUENCY (MHz)
Figure 54. AD9861 Tx Path FFT of OFDM Signal in Figure 52,
with 1× Interpolation
Figure 57. AD9861 Tx Path FFT of OFDM Signal in Figure 52,
with 4× Interpolation
Rev. A | Page 18 of 51
Data Sheet
AD9861
Figure 58 to Figure 63 use the same input data to the Tx path, a 256-carrier OFDM signal over a 1.75 MHz bandwidth, centered at 7 MHz. The
center four carriers are removed from the signal to observe the in-band intermodulation distortion (IMD) from the DAC output.
–40
–40
–50
–50
–60
–60
–70
–70
–80
–80
–90
–90
–100
–110
–120
–130
–140
–100
–110
–120
–130
–140
6.0
6.2
6.4
6.6
6.8
7.0
7.2
7.4
7.6
7.8
8.0
6.97
6.98
6.99
7.00
7.01
7.02
7.03
FREQUENCY (MHz)
FREQUENCY (MHz)
Figure 58. AD9861 Tx Path FFT, 256-Carrier (Center Four Carriers Removed)
OFDM Signal over 1.75 MHz Bandwidth, Centered at 7 MHz, with
20 mA Full-Scale Output into 60 Ω Differential Load
Figure 61. AD9861 Tx Path FFT, In-Band IMD Products of
OFDM Signal in Figure 58
–40
–50
–40
–50
–60
–60
–70
–70
–80
–80
–90
–90
–100
–110
–120
–130
–140
–100
–110
–120
–130
–140
6.06
6.08
6.10
6.12
6.14
6.16
6.18
7.81
7.83
7.85
7.87
7.89
7.91
7.93
FREQUENCY (MHz)
FREQUENCY (MHz)
Figure 59. AD9861 Tx Path FFT, Lower-Band IMD Products of
OFDM Signal in Figure 58
Figure 62. AD9861 Tx Path FFT, Upper-Band IMD Products of
OFDM Signal in Figure 52
–30
–40
–50
–60
–70
–80
–90
–30
–40
–50
–60
–70
–80
–90
–100
–100
–110
–120
–130
–110
–120
–130
0
5
10
15
20
25
0
5
10
15
20
25
FREQUENCY (MHz)
FREQUENCY (MHz)
Figure 60. AD9861 Tx Path FFT of OFDM Signal in Figure 52,
with 1× Interpolation
Figure 63. AD9861 Tx Path FFT of OFDM Signal in Figure 52,
with 4× Interpolation
Rev. A | Page 19 of 51
AD9861
Data Sheet
Figure 64 to Figure 69 use the same input data to the Tx path, a 256-carrier OFDM signal over a 23 MHz bandwidth, centered at 23 MHz. The
center four carriers are removed from the signal to observe the in-band intermodulation distortion (IMD) from the DAC output.
–40
–40
–50
–50
–60
–60
–70
–70
–80
–80
–90
–90
–100
–110
–120
–130
–140
–100
–110
–120
–130
–140
9
14
19
24
29
34
22.6
22.7
22.8
22.9
23.0
23.1
23.2
23.3
23.4
FREQUENCY (MHz)
FREQUENCY (MHz)
Figure 64. AD9861 Tx Path FFT, 256-Carrier (Center Four Carriers Removed)
OFDM Signal over 23 MHz Bandwidth, Centered at 7 MHz, with
20 mA Full-Scale Output into 60 Ω Differential Load
Figure 67. AD9861 Tx Path FFT, In-Band IMD Products of
OFDM Signal in Figure 64
–40
–50
–40
–50
–60
–60
–70
–70
–80
–80
–90
–90
–100
–110
–120
–130
–140
–100
–110
–120
–130
–140
33.5 33.7 33.9 34.1 34.3 34.5 34.7 34.9 35.1 35.3 35.5
FREQUENCY (MHz)
10.5 10.7 10.9 11.1 11.3 11.5 11.7 11.9 12.1 12.3 12.5
FREQUENCY (MHz)
Figure 65. AD9861 Tx Path FFT, Lower-Band IMD Products of
OFDM Signal in Figure 64
Figure 68. AD9861 Tx Path FFT, Upper-Band IMD Products of
OFDM Signal in Figure 64
–30
–40
–30
–40
–50
–60
–70
–80
–90
–50
–60
–70
–80
–90
–100
–110
–120
–130
–100
–110
–120
–130
0
10
20
30
40
50
60
70
80
90
0
10
20
30
40
50
60
70
80
90
FREQUENCY (MHz)
FREQUENCY (MHz)
Figure 66. AD9861 Tx Path FFT of OFDM Signal in Figure 52
with 1× Interpolation
Figure 69. AD9861 Tx Path FFT of OFDM Signal in Figure 52
with 4× Interpolation
Rev. A | Page 20 of 51
Data Sheet
AD9861
TERMINOLOGY
Input Bandwidth
Harmonic Distortion, Second
The analog input frequency at which the spectral power of the
fundamental frequency (as determined by the FFT analysis) is
reduced by 3 dB.
The ratio of the rms signal amplitude to the rms value of the
second harmonic component, reported in dBc.
Harmonic Distortion, Third
Aperture Delay
The ratio of the rms signal amplitude to the rms value of the
third harmonic component, reported in dBc.
The delay between the 50% point of the rising edge of the CLKIN
signal and the instant at which the analog input is actually sampled.
Integral Nonlinearity
Aperture Uncertainty (Jitter)
The sample-to-sample variation in aperture delay.
The deviation of the transfer function from a reference line
measured in fractions of an LSB using a “best straight line”
determined by a least square curve fit.
Crosstalk
Coupling onto one channel being driven by a –0.5 dBFS signal when
the adjacent interfering channel is driven by a full-scale signal.
Minimum Conversion Rate
The encode rate at which the SNR of the lowest analog signal
frequency drops by no more than 3 dB below the guaranteed
limit.
Differential Analog Input Voltage Range
The peak-to-peak differential voltage that must be applied to the
converter to generate a full-scale response. Peak differential voltage
is computed by observing the voltage on a single pin and subtracting
the voltage from the other pin, which is 180° out of phase. Peak-to-
peak differential is computed by rotating the input phase 180° and
taking the peak measurement again. Then the difference is
computed between both peak measurements.
Maximum Conversion Rate
The encode rate at which parametric testing is performed.
Output Propagation Delay
The delay between a differential crossing of CLK+ and CLK−
and the time when all output data bits are within valid logic
levels.
Differential Nonlinearity
The deviation of any code width from an ideal 1 LSB step.
Power Supply Rejection Ratio
The ratio of a change in input offset voltage to a change in
power supply voltage.
Effective Number of Bits (ENOB)
The effective number of bits is calculated from the measured SNR
based on the following equation:
Signal-to-Noise and Distortion (SINAD)
The ratio of the rms signal amplitude (set 1 dB below full-scale)
to the rms value of the sum of all other spectral components,
including harmonics, but excluding dc.
SNRMEASURED −1.76 dB
ENOB =
6.02
Pulse Width/Duty Cycle
Signal-to-Noise Ratio (without Harmonics)
Pulse width high is the minimum amount of time that a signal must
be left in the logic high state to achieve rated performance; pulse
width low is the minimum time a signal must be left in the low state,
logic low.
The ratio of the rms signal amplitude (set at 1 dB below full
scale) to the rms value of the sum of all other spectral
components, excluding the first five harmonics and dc.
Spurious-Free Dynamic Range (SFDR)
Full-Scale Input Power
Expressed in dBm, full-scale input power is computed using the
following equation:
The ratio of the rms signal amplitude to the rms value of the
peak spurious spectral component. The peak spurious
component may or may not be a harmonic. It also may be
reported in dBc (i.e., degrades as signal level is lowered) or
dBFS (i.e., always related back to converter full scale). SFDR
does not include harmonic distortion components.
2
VFULLSCALE −RMS ZINPUT
PowerFULLSCALE =10log
0.001
Gain Error
Worst Other Spur
Gain error is the difference between the measured and ideal full-
scale input voltage range of the ADC.
The ratio of the rms signal amplitude to the rms value of the
worst spurious component (excluding the second and third
harmonics) reported in dBc.
Rev. A | Page 21 of 51
AD9861
Data Sheet
THEORY OF OPERATION
The differential input stage is dc self-biased and allows
SYSTEM BLOCK
differential or single-ended inputs. The output-staging block
aligns the data, carries out the error correction, and passes the
data to the output buffers.
The AD9861 is targeted to cover the mixed-signal front end needs of
multiple wireless communication systems. It features a receive path
that consists of dual 10-bit receive ADCs, and a transmit path that
consists of dual 10-bit transmit DACs (TxDAC). The AD9861
integrates additional functionality typically required in most
systems, such as power scalability, additional auxiliary converters, Tx
gain control, and clock multiplication circuitry.
The latency of the Rx path is about 5 clock cycles.
Rx Path Analog Input Equivalent Circuit
The Rx path analog inputs of the AD9861 incorporate a novel
structure that merges the function of the input sample-and-hold
amplifiers (SHAs) and the first pipeline residue amplifiers into a
single, compact switched capacitor circuit. This structure
achieves considerable noise and power savings over a conven-
tional implementation that uses separate amplifiers by eliminating
one amplifier in the pipeline.
The AD9861 minimizes both size and power consumption to
address the needs of a range of applications from the low power
portable market to the high performance base station market. The
part is provided in a 64-lead lead frame chip scale package (LFCSP)
that has a footprint of only 9 mm × 9 mm. Power consumption can
be optimized to suit the particular application beyond just a speed
grade option by incorporating power-down controls, low power
ADC modes, TxDAC power scaling, and a half-duplex mode, which
automatically disables the unused digital path.
Figure 70 illustrates the equivalent analog inputs of the AD9861
(a switched capacitor input). Bringing CLK to logic high opens
switch S3 and closes switches S1 and S2; this is the sample mode
of the input circuit. The input source connected to VIN+ and
VIN− must charge capacitor CH during this time. Bringing CLK
to a logic low opens S2, and then switch S1 opens followed by
closing S3. This puts the input circuit into hold mode.
The AD9861 uses two 10-bit buses to transfer Rx path data and Tx
path data. These two buses support 20-bit parallel data transfers or
10-bit interleaved data transfers. The bus is configurable through
either external mode pins or through internal registers settings. The
registers allow many more options for configuring the entire device.
S1
C
H
VIN+
+
C
R
R
IN
IN
The following sections discuss the various blocks of the AD9861: Rx
block, Tx block, the auxiliary converters, the digital block,
programmable registers and the clock distribution block.
S3
S2
V
CM
C
IN
H
–
VIN–
C
IN
Rx PATH BLOCK
03606-0-002
Rx Path General Description
Figure 70. Differential Input Architecture
The AD9861 Rx path consists of two 10-bit, 50 MSPS (for the
AD9861-50) or 80 MSPS (for the AD9861-80) analog-to-digital
converters (ADCs). The dual ADC paths share the same clocking
and reference circuitry to provide optimal matching characteristics.
Each of the ADCs consists of a 9-stage differential pipelined
switched capacitor architecture with output error correction logic.
The structure of the input SHA places certain requirements on
the input drive source. The differential input resistors are
typically 2 kΩ each. The combination of the pin capacitance,
CIN, and the hold capacitance, CH, is typically less than 5 pF. The
input source must be able to charge or discharge this capaci-
tance to 10-bit accuracy in one-half of a clock cycle. When the
SHA goes into sample mode, the input source must charge or
discharge capacitor CH from the voltage already stored on it to
the new voltage. In the worst case, a full-scale voltage step on
the input source must provide the charging current through the
The pipelined architecture permits the first stage to operate on a new
input sample, while the remaining stages operate on preceding
samples. Sampling occurs on the falling edge of the input clock. Each
stage of the pipeline, excluding the last, consists of a low resolution
flash ADC and a residual multiplier to drive the next stage of the
pipeline. The residual multiplier uses the flash ADC output to
control a switched capacitor digital-to-analog converter (DAC) of
the same resolution. The DAC output is subtracted from the stage’s
input signal, and the residual is amplified (multiplied) to drive the
next pipeline stage. The residual multiplier stage is also called a
multiplying DAC (MDAC). One bit of redundancy is used in each
one of the stages to facilitate digital correction of flash errors. The
last stage simply consists of a flash ADC.
RON of switch S1 (typically 100 Ω) to a settled voltage within
one-half of the ADC sample period. This situation corresponds
to driving a low input impedance. On the other hand, when the
source voltage equals the value previously stored on CH, the
hold capacitor requires no input current and the equivalent
input impedance is extremely high.
Rev. A | Page 22 of 51
Data Sheet
AD9861
Rx Path Application Section
REFT = AVDD/2 + 0.5 V
REFB = AVDD/2 – 0.5 V
Adding series resistance between the output of the signal source and
the VIN pins reduces the drive requirements placed on the signal
source. Figure 71 shows this configuration.
AD9861
REFT
0.1µF
0.1µF
AD9861
TO ADCs
R
10µF
SERIES
REFB
VIN+
0.1µF
C
SHUNT
VREF
0.1µF
VIN–
R
SERIES
10µF
0.5V
03606-0-003
Figure 71. Typical Input
The bandwidth of the particular application limits the size of this
resistor. For applications with signal bandwidths less than 10 MHz,
the user may insert series input resistors and a shunt capacitor to
produce a low-pass filter for the input signal. Additionally, adding a
shunt capacitance between the VIN pins can lower the ac load
impedance. The value of this capacitance depends on the source
resistance and the required signal bandwidth.
03606-0-020
Figure 72. Typical Rx Path Decoupling
An external reference may be used for systems that require a
different input voltage range, high accuracy gain matching
between multiple devices, or improvements in temperature drift
and noise characteristics. When an external reference is desired,
the internal Rx band gap reference must be powered down
using the VREF2 register [Register 0x5, Bit 4] and the external
reference driving the voltage level on the VREF pin. The
external voltage level must be one-half of the desired peak-to-
peak differential voltage swing. The result is that the differential
voltage references are driven to new voltages:
The Rx input pins are self-biased to provide this midsupply,
common-mode bias voltage, so it is recommended to ac couple the
signal to the inputs using dc blocking capacitors. In systems that
must use dc coupling, use an op amp to comply with the input
requirements of the AD9861. The inputs accept a signal with a 2 V
p-p differential input swing centered about one-half of the supply
voltage (AVDD/2). If the dc bias is supplied externally, the internal
input bias circuit must be powered down by writing to registers
Rx_A dc bias [Register 0x3, Bit 6] and Rx_B dc bias [Register 0x4,
Bit 7].
REFT = AVDD/2 +VREF/2 V
REFB = AVDD/2 – VREF/2 V
If an external reference is used, it is recommended not to exceed
a differential offset voltage for the reference greater than 1 V.
The ADCs in the AD9861 are designed to sample differential input
signals. The differential input provides improved noise immunity
and better THD and SFDR performance for the Rx path. In systems
that use single-ended signals, these inputs can be digitized, but it is
recommended that a single-ended-to-differential conversion be
performed. A single-ended-to-differential conversion can be
performed by using a transformer coupling circuit (typically for
signals above 10 MHz) or by using an operational amplifier, such as
the AD8138 (typically for signals below 10 MHz).
Clock Input and Considerations
Typical high speed ADCs use both clock edges to generate a
variety of internal timing signals and, as a result, may be
sensitive to clock duty cycle. Commonly, a 5% tolerance is
required on the clock duty cycle to maintain dynamic perform-
ance characteristics. The AD9861 contains clock duty cycle
stabilizer circuitry (DCS). The DCS retimes the internal ADC
clock (nonsampling edge) and provides the ADC with a
nominal 50% duty cycle. Input clock rates of over 40 MHz can
use the DCS so that a wide range of input clock duty cycles can be
accommodated. Conversely, DCS must not be used for Rx
sampling below 40 MSPS. Maintaining a 50% duty cycle clock is
particularly important in high speed applications when proper
sample-and-hold times for the converter are required to
maintain high performance. The DCS can be enabled by
writing highs to the Rx_A/Rx_B CLK duty register bits
[Register 0x06/0x07, Bit 4].
ADC Voltage References
The AD9861 10-bit ADCs use internal references that are designed
to provide for a 2 V p-p differential input range. The internal band
gap reference generates a stable 1 V reference level and is decoupled
through the VREF pin. REFT and REFB are the differential
references generated based on the voltage level of VREF. Figure 72
shows the proper decoupling of the reference pins VREF, REFT, and
REFB when using the internal reference. Decoupling capacitors must
be placed as close to the reference pins as possible.
The duty cycle stabilizer uses a delay-locked loop to create the
nonsampling edge. As a result, any changes to the sampling
frequency require approximately 2 µs to 3 µs to allow the DLL
to adjust to the new rate and settle. High speed, high resolution
ADCs are sensitive to the quality of the clock input.
External references REFT and REFB are centered at AVDD/2 with a
differential voltage equal to the voltage at VREF (by default 1 V
when using the internal reference), allowing a peak-to-peak
differential voltage swing of 2× VREF. For example, the default 1 V
VREF reference accepts a 2 V p-p differential input swing and the
offset voltage must be
Rev. A | Page 23 of 51
AD9861
Data Sheet
The degradation in SNR at a given full-scale input frequency (fINPUT),
due only to aperture jitter (tA), can be calculated with the following
equation:
When either or both of the channel paths are enabled after a
power-down, the wake-up time is directly related to the
recharging of the REFT and REFB decoupling capacitors and
the duration of the power-down. Typically, it takes approxi-
mately 5 ms to restore full operation with fully discharged 0.1 µF
and 10 µF decoupling capacitors on REFT and REFB.
SNR degradation = 20 log [(½)πFINtA)]
In the equation, the rms aperture jitter, tA, represents the root-sum-
square of all jitter sources, which includes the clock input, analog
input signal, and ADC aperture jitter specification. Undersampling
applications are particularly sensitive to jitter. The clock input is a
digital signal that must be treated as an analog signal with logic level
threshold voltages, especially in cases where aperture jitter may
affect the dynamic range of the AD9861. Power supplies for clock
drivers must be separated from the ADC output driver supplies to
avoid modulating the clock signal with digital noise. Low jitter
crystal-controlled oscillators make the best clock sources. If the
clock is generated from another type of source (by gating, dividing,
or other methods), it must be retimed by the original clock at the last
step.
Tx PATH BLOCK
The AD9861 transmit (Tx) path includes dual interpolating
10-bit current output DACs that can be operated independently
or can be coupled to form a complex spectrum in an image
reject transmit architecture. Each channel includes two FIR
filters, making the AD9861 capable of 1×, 2×, or 4× interpola-
tion. High speed input and output data rates can be achieved
within the limitations of Table 9.
Table 9. AD9861 Tx Path Maximum Data Rate
Input Data
Rate per
DAC
Sampling
Rate
Power Dissipation and Standby Mode
Interpolation 20-Bit Interface Channel
Rate
Mode
(MSPS)
(MSPS)
The power dissipation of the AD9861 Rx path is proportional to its
sampling rate. The Rx path portion of the digital (DRVDD) power
dissipation is determined primarily by the strength of the digital
drivers and the load on each output bit. The digital drive current can
be calculated by
FD, HD10, Clone 80
HD20
FD, HD10, Clone 80
HD20
FD, HD10, Clone 50
HD20 50
80
1×
160
160
160
160
200
200
2×
4×
80
IDRVDD = VDRVDD × CLOAD × fCLOCK × N
where N is the number of bits changing and CLOAD is the average load
on the digital pins that changed.
By using the dual DAC outputs to form a complex signal, an
external analog quadrature modulator, such as the Analog
Devices AD8349, can enable an image rejection architecture.
(Note: the AD9861 evaluation board includes a quadrature
modulator in the Tx path that accommodates the AD8345,
AD8346 and the AD8345 footprints.) To optimize the image
rejection capability, as well as LO feedthrough suppression in
this architecture, the AD9861 offers programmable (via the SPI
port) fine (trim) gain and offset adjustment for each DAC.
The analog circuitry is optimally biased so that each speed grade
provides excellent performance while affording reduced power
consumption. Each speed grade dissipates a baseline power at low
sample rates, which increases with clock frequency. The baseline
power dissipation for either speed grade can be reduced by asserting
the ADC_LO_PWR pin, which reduces internal ADC bias currents
by half, in some case resulting in degraded performance.
To further reduce power consumption of the ADC, the
Also included in the AD9861 are a phase-locked loop (PLL)
clock multiplier and a 1.2 V band gap voltage reference. With
the PLL enabled, a clock applied to the CLKIN input is multi-
plied internally and generates all necessary internal synchronization
clocks. Each 10-bit DAC provides two complementary current
outputs whose full-scale currents can be determined from a
single external resistor.
ADC_LO_PWR pin can be combined with a serial programmable
register setting to configure an ultralow power mode. The ultralow
power mode reduces the power consumption by a fourth of the
normal power consumption. The ultralow power mode can be used
at slower sampling frequencies or if reduced performance is
acceptable. To configure the ultralow power mode, assert the
ADC_LO_PWR pin and write the following register settings:
An external pin, TxPWRDWN, can be used to power down the
Tx path, when not used, to optimize system power consumption.
Using the TxPWRDWN pin disables clocks and some analog
circuitry, saving both digital and analog power. The power-down
mode leaves the biases enabled to facilitate a quick recovery
time, typically <10 µs. Additionally, a sleep mode is available,
which turns off the DAC output current, but leaves all other
circuits active, for a modest power savings. An SPI compliant
serial port is used to program the many features of the AD9861.
Note that in power-down mode, the SPI port is still active.
Register 0x08
Register 0x09
Register 0x0A
(MSB) ‘0000 1100’
(MSB) ‘0111 0000’
(MSB) ‘0111 0000’
Either of the ADCs in the AD9861 Rx path can be placed in standby
mode independently by writing to the appropriate SPI register bits in
Registers 3, 4, and 5. The minimum standby power is achieved when
both channels are placed in full power-down mode using the
appropriate SPI register bits in Registers 3, 4, and 5. Under this
condition, the internal references are powered down.
Rev. A | Page 24 of 51
Data Sheet
AD9861
DAC Equivalent Circuits
1.2V
REFERENCE
DAC A AND DAC B
REFERENCE BIASES
The AD9861 Tx path consisting of dual 10-bit DACs is shown in
Figure 73. The DACs integrate a high performance TxDAC core, a
programmable gain control through a programmable gain amplifier
(TxPGA), coarse gain control, and offset adjustment and fine gain
control to compensate for system mismatches. Coarse gain applies a
gross scaling to either DAC by 1×, (1/2)×, or (1/11)×. The TxPGA
provides gain control from 0 dB to
I
OUTFSMAX
REFIO
FSADJ
CURRENT
SOURCE ARRAY
I
REF
0.1µF
R
≥ 4kΩ
SET
03606-0-005
–20 dB in steps of 0.1 dB and is controlled via the 8-bit TxPGA
setting. A fine gain adjustment of 4% for each channel is controlled
through a 6-bit fine gain register. By default, coarse gain is 1×, the
TxPGA is set to 0 dB, and the fine gain is set to 0%.
Figure 74. Reference Circuitry
Referring to the transfer function of the following equation,
OUTFSMAX is the maximum current output of the DAC with the
default gain setting (0 dB), and is based on a reference current,
REF. IREF is set by the internal 1.2 V reference and the external
SET resistor.
OUTFSMAX = 64 × (REFIO/RSET
I
The TxDAC core of the AD9861 provides dual, differential,
complementary current outputs generated from the 10-bit data. The
10-bit dual DACs support update rates up to 200 MSPS. The
differential outputs (IOUT+ and IOUT–) of each dual DAC are
complementary, meaning that they always add up to the full-scale
current output of the DAC, IOUTFS. Optimum ac performance loads or
a transformer.
I
R
I
)
Typically, RSET is 4 kΩ, which sets IOUTFSMAX to 20 mA, the
optimal dynamic setting for the TxDACs. Increasing RSET by a
factor of 2 proportionally decreases IOUTFSMAX by a factor of 2.
I
OUTFSMAX of each DAC can be rescaled either simultaneously
OFFSET
DAC
using the TxPGA gain register or independently using the
DAC A/DAC B coarse gain registers.
+
IOUT+A
+
TxDAC
PGA
+
The TxPGA function provides 20 dB of simultaneous gain
range for both DACs, and is controlled by writing to the SPI
register TxPGA gain for a programmable full-scale output of
10% to 100% of IOUTFSMAX. The gain curve is linear in dB, with
steps of about 0.1 dB. Internally, the gain is controlled by
changing the main DAC bias currents with an internal TxPGA
DAC whose output is heavily filtered via an on-chip R-C filter
to provide continuous gain transitions. Note that the settling
time and bandwidth of the TxPGA DAC can be improved by a
factor of 2 by writing to the TxPGA fast register.
IOUT–A
+
REFERENCE
BIAS
+
IOUT+B
IOUT–B
TxDAC
PGA
+
+
+
OFFSET
DAC
03606-0-004
Each DAC has independent coarse gain control. Coarse gain
control can be used to accommodate different IOUTFS from the
dual DACs. The coarse full-scale output control can be adjusted
by using the DAC A/DAC B coarse gain registers to 1/2 or 1/11
of the nominal full-scale current.
Figure 73. TxDAC Output Structure Block Diagram
The fine gain control provides improved balance of QAM modulated
signals, resulting in improved modulation accuracy and image
rejection.
Fine gain controls and dc offset controls can be used to
compensate for mismatches (for system level calibration),
allowing improved matching characteristics of the two Tx
channels and aiding in suppressing LO feedthrough. This is
especially useful in image rejection architectures. The 10-bit dc
offset control of each DAC can be used independently to
provide an offset of up to 12% of IOUTFSMAX to either differential
pin, thus allowing calibration of any system offsets. The fine
gain control with 5-bit resolution allows the IOUTFSMAX of each
DAC to be varied over a 4% range, allowing compensation of
any DAC or system gain mismatches. Fine gain control is set
through the DAC A/DAC B fine gain registers, and the offset
control of each DAC is accomplished using the DAC A/DAC B
offset registers.
The independent DAC A and DAC B offset control adds a small dc
current to either IOUT+ or IOUT– (not both). The selection of
which IOUT this offset current is directed toward is programmable
via register setting. Offset control can be used for suppression of an
LO leakage signal that typically results at the output of the
modulator. If the AD9861 is dc-coupled to an external modulator,
this feature can be used to cancel the output offset on the AD9861 as
well as the input offset on the modulator. The reference circuitry is
shown in Figure 74.
Rev. A | Page 25 of 51
AD9861
Data Sheet
Clock Input Configuration
The sleep mode, when activated, turns off the DAC output
currents, but the rest of the chip remains functioning. When
coming out of sleep mode, the AD9861 immediately returns to
full operation.
The quality of the clock and data input signals is important in
achieving optimum performance. The external clock driver circuitry
provides the AD9861 with a low jitter clock input that meets the
min/max logic levels while providing fast edges. When a driver is
used to buffer the clock input, it must be placed very close to the
AD9861 clock input, thereby negating any transmission line effects
such as reflections due to mismatch.
A full power-down mode can be enabled through the SPI
register, which turns off all Tx path related analog and digital
circuitry in the AD9861. When returning from full power-
down mode, enough clock cycles must be allowed to flush the
digital filters of random data acquired during the power-down
cycle.
Programmable PLL
CLKIN can function either as an input data rate clock (PLL enabled)
or as a DAC data rate clock (PLL disabled).
Interpolation Stage
Interpolation filters are available for use in the AD9861 transmit
path, providing 1× (bypassed), 2×, or 4× interpolation.
The PLL clock multiplier and distribution circuitry produce the
necessary internal timing to synchronize the rising edge triggered
latches for the enabled interpolation filters and DACs. This circuitry
consists of a phase detector, charge pump, voltage controlled
oscillator (VCO), and clock distribution block, all under SPI port
control. The charge pump, phase detector, and VCO are powered
from PLL_AVDD, while the clock distribution circuits are powered
from the DVDD supply.
The interpolation filters effectively increase the Tx data rate
while suppressing the original images. The interpolation filters
digitally shift the worst-case image further away from the
desired signal, thus reducing the requirements on the analog
output reconstruction filter.
There are two 2× interpolation filters available in the Tx path.
An interpolation rate of 4× is achieved using both interpolation
filters; an interpolation rate of 2× is achieved by enabling only
the first 2× interpolation filter.
To ensure optimum phase noise performance from the PLL clock
multiplier circuits, PLL_AVDD must originate from a clean analog
supply. The speed of the VCO within the PLL also has an effect on
phase noise.
The first interpolation filter provides 2× interpolation using a
39-tap filter. It suppresses out-of-band signals by 60 dB or more
and has a flat pass-band response (less than 0.1 dB ripple)
extending to 38% of the input Tx data rate (19% of the DAC
update rate, fDAC). The maximum input data rate is 80 MSPS per
channel when using 2× interpolation.
The PLL locks with VCO speeds as low as 32 MHz up to 350 MHz,
but optimal phase noise with respect to VCO speed is achieved by
running it in the range of 64 MHz to 200 MHz.
Power Dissipation
The AD9861 Tx path power is derived from three voltage supplies:
AVDD, DVDD, and DRVDD.
The second interpolation filter provides an additional 2× interpola-
tion for an overall 4× interpolation. The second filter is a 15-tap
filter, which suppresses out-of-band signals by 60 dB or more.
IDRVDD and IDVDD are very dependent on the input data rate, the
interpolation rate, and the activation of the internal digital
modulator. IAVDD has the same type of sensitivity to data,
interpolation rate, and the modulator function, but to a much lesser
degree (< 10%).
The flat pass-band response (less than 0.1 dB attenuation) is
38% of the Tx input data rate (9.5% of fDAC). The maximum
input data rate per channel is 50 MSPS per channel when using
4× interpolation.
Sleep/Power-Down Modes
Latch/Demultiplexer
The AD9861 provides multiple methods for programming power
saving modes. The externally controlled TxPWRDWN or SPI
programmed sleep mode and full power-down mode are the main
options.
Data for the dual-channel Tx path can be latched in parallel
through two ports in half-duplex operations (HD20 mode) or
through a single port by interleaving the data (FD, HD10, and
Clone modes). See the Flexible I/O Interface Options section in
the Digital Block description and the Clock Distribution Block
section for further descriptions of each mode.
TxPWRDWN is used to disable all clocks and much of the analog
circuitry in the Tx path when asserted. In this mode, the biases
remain active, therefore reducing the time required for re-enabling
the Tx path. The time of recovery from power-down for this mode is
typically less than 10 µs.
Rev. A | Page 26 of 51
Data Sheet
AD9861
Another synchronization mode allows any combination of
AuxDACs to be updated along with an externally applied rising
edge to the TxPwrDwn pin.
AUXILIARY CONVERTERS
The AD9861 contains auxiliary analog-to-digital converters
(AuxADCs) and auxiliary digital-to-analog converters (AuxDACs).
These auxiliary converters can be used to measure or force system-
wide control signals.
Typical settling time for the AuxDAC output is less than 0.5 µs,
but is dependent on the load.
Auxiliary ADCs
By default, the auxiliary converters are disabled and powered down.
Enabling and controlling the auxiliary converters is achieved
through the serial programmable registers.
Two auxiliary 10-bit SAR analog-to-digital converters
(AuxADCs) are available for monitoring various external
signals throughout the system, such as a receive signal strength
indicator (RSSI) function or temperature indicator. The
AuxADCs have many SPI programmable options. Register
settings can be used to configure various full-scale reference
options, change the sampling rate, and average multiple sample
readings. By default, the AuxADC start conversion and output
value is accessed through the register map. Additionally an
auxiliary serial port can be enabled and used to initiate a
conversion and read back the AuxADC data. The auxiliary
serial port interface is available so that the normal SPI can be
used to program other options while the AuxADC is accessed.
Pins 29, 30, and 46 are configurable either as AuxDAC outputs or as
AuxADC inputs. The respective AuxADC inputs are connected to
the external pin when a conversion is initiated and are disconnected
when the conversion is complete. The AuxDAC outputs are enabled
by writing to the respective power-up registers in Register 0x29.
•
•
•
Pin 29 can be connected to AuxDAC_A and/or AuxADC_A
Channel 2.
Pin 30 can be connected to AuxDAC_B and/or AuxADC_A
Channel 1.
Pin 46 can be connected to AuxDAC_C and/or AuxADC_B.
By default, the AuxADCs are powered down and automatically
powered up when a conversion is initiated.
Auxiliary DACs
The AD9861 integrates three 8-bit voltage output auxiliary digital-
to-analog converters (AuxDACs), which can be used for supplying
various control voltages throughout the system such as a VCXO
voltage control or external VGA gain control. The AuxDACs have a
programmable full-scale output voltage, VOUTFS, and can be
synchronized to update with a single register write or a rising edge
on the TxPwrDwn pin.
The two AuxADCs (AuxADC_A and AuxADC_B) can monitor
up to three system signals. AuxADC_A has multiplexed inputs
that control whether pin AUX_ADC_A1 or pin AUX_ADC_A2
is connected to the input of AuxADC_A. The multiplexer is
programmed through Register 0x22, Bit 1, SelectA. By default,
the register is low, which connects the AUX_ADC_A2 pin to
the input.
By default, the AuxDAC outputs are powered down and require a
serial write to the power-up registers [Register 0x29, Bits 2–0] to
enable them.
The full-scale AuxADC reference can be generated from the
analog supply (supply dependent), an internal reference, or
from an external applied reference. Table 10 shows the register
settings required to select the AuxADC full-scale reference.
The full-scale output of each AuxDAC is independently
programmable to the full scales of 2.5 V, 2.7 V, 3.0 V, or 3.3 V by
using Serial Register 0x17. The AuxDAC outputs have an I-to-V
driver that produces a voltage output that settles to 1 LSB within 0.5
µs. The output driver is capable of sinking or sourcing up to 6 mA.
Using the AuxDAC requires the SPI to be operational.
By default, an internal reference provides a buffered full-scale
reference for both of the AuxADCs, which is equal to the supply
voltage for the AuxADCs (PLL_AVDD). A supply independent
2.5 V or 3.0 V internal full-scale reference can be enabled by
writing to register AuxADC Ref Enable and AuxADC Ref FS in
Register 0x17. This internal reference is based on the main Rx
path ADC VREF voltage, so it requires the main Rx path VREF
to be enabled.
The AuxDACs are based on a resistor divider network. The
AuxDACs output level is proportional to the straight binary input
codes from the appropriate SPI registers, Registers 0x24 to 0x26. By
default, the AuxDAC output is updated immediately following the
register write, but the update can occur synchronously to a single
register write or to the TxPwrDwn rising edge.
Another AuxADC full-scale reference option is an externally
supplied full-scale reference. The external reference can be
applied to either or both of the AuxADCs by setting the
appropriate bit(s) in Registers 0x22 and 0x17. Setting either or
both of these bits high disconnects the internal reference buffer
and enables the externally applied reference from the
AuxADC_Ref pin to the respective channel(s).
In slave mode, the AuxDAC update occurs when a logic high is
written to the appropriate update registers [Register 0x28, Bits 2–0,
Update C, B, and A]. Slave mode is enabled by writing a high to the
slave mode register bit [Register 0x28, Bit 7, Slave Enable].
Rev. A | Page 27 of 51
AD9861
Data Sheet
Table 10. Configuring AuxADC Reference
Refsel A/B
AuxADC_A Reference
Configuration
AuxADC Ref Enable
[Register 0x17, Bit 1]
AuxADC Ref FS
[Register 0x17, Bit 0]
[Register 0x22,
Bit 2/Bit 5]
Notes
Buffered PLL_VDD
0
1
0
0
0
1
Default mode.
Internal 3.0 V (3 x VREF)
Decouple at AUXADC_REF pin.
VREF voltage from Rx path.
Internal 2.5 V (2.5 x VREF)
Externally forced
1
0
1
1
1
Decouple at AUXADC_REF pin.
Don't Care
Force and decouple at
AUXADC_REF pin.
The AuxADCs can convert at rates of up to 5.33 MSPS (0.1875 µs
maximum conversion time) and have a bandwidth of around 200
kHz. The conversion time, including setup, requires 12 clock cycles.
The maximum clock rate for the AuxADCs is 64 MHz and is
generated from a divided down Rx ADC clock. The divide down
ratio is controlled by register AuxADC Clock Div [Register 0x23,
Bits 1, 0]. By default, the Rx ADC clock is divided by 4. At an Rx
ADC rate greater than 64 MHz, the AuxADC Clock Div register
must be set to divide-by-2 or divide-by-4.
The AuxSPI can be enabled and configured by setting register
AuxSPI enable [Register 0x22, Bit 7]. Also required is that the
normal serial port interface be configured for 3-wire mode (the
SPI_SDO pin must be disabled to use the Aux_SPI_SDO pin)
by setting the SDIO BiDir register bit [Register 0x00, Bit 7].
Register bit Sel BnotA [Register 0x22, Bit 6] configures whether
AuxADC_A or AuxADC_B is controlled by the AuxSPI.
AuxADC_A has two inputs: AuxADC_A1 and AuxADC_A2.
Setting the Select A bit [Register 0x22, Bit 1] determines which
of the multiplexed inputs is connected to AuxADC_A.
On-chip averaging of 2, 4, 8, 16, 32, or 64 samples can be enabled
through Register 0x18 for AuxADC_A or through Register 0x19 for
AuxADC_B. When the averaging option is enabled, the AuxADC
continually converts the number of samples specified and outputs
the average value.
The AuxSPI consists of a chip select pin (AUX_SPI_CS, pin
number 4), a clock pin (AUX_SPI_CLK), and a data output pin
(AUX_SPI_SDO multiplex with the SPI_SDO pin). A conversion
is initiated by pulsing the AUX_SPI_CS pin low (AUX_SPI_CS
must remain low during the entire conversion cycle, including
the readback phase). When the conversion is complete, the data
pin, AUX_SPI_SDO, transitions from a logic low to a logic
high. At this point, the user supplies an external clock on the
AUX_SPI_CLK pin. The AUX_SPI_CLK pin must be tied low
when not in use. No data is present on the first rising edge. The
data output bit is updated on the falling edge of the clock pulse
and is settled by and can be latched on the next clock rising
edge. The data arrives serially, MSB first. The AuxSPI runs at a
rate up to 16 MHz.
There are three modes of operating the AuxADC: SPI operation
mode (default), SPI with external start convert operation mode, and
Aux_SPI operation mode.
In the default SPI operation mode, a conversion is initiated by
writing a logic high to one or both of the start register bits, Start A or
Start B [Register 0x22, Bit 0 or Bit 3]. If AuxADC is configured as
averaging mode, the proper start bit is the Start Average AuxADC
A/B register [Register 0x18, Bit 7/Register 0x19, Bit 7].
When the conversion is complete, the straight binary, 10-bit output
data of the AuxADC is written to one of three reserved locations in
the register map, depending on which AuxADC and which
multiplexed input is selected. Because the AuxADCs output 10 bits,
two register addresses are needed for each data location.
Operation of the Aux_SPI requires that 3-wire SPI mode be
used, disabling the SDO pin. If the controller is a 4-wire
interface, a method of connecting the 3-wire AD9861 interface
to the 4-wire controller is suggested in Figure 75.
In the optional SPI with external start convert operation mode, the
conversion is initiated by asserting AuxSPI_csb, and data retrieval is
accomplished through the SPI interface (data retrieval is similar to
the default operation). The AuxSPI_csb can be configured to initiate
the conversion of either one of the AuxADCs. This mode is
configured by setting the AuxSPI enable register bit [Register 0x22,
Bit 7].
An example of an AuxSPI access is shown in Figure 75. In the
AuxSPI configuration, a start convert is initiated by applying a
rising edge to the Aux_SPI_CS pin. A rising edge on the
Aux_SPI_DO pin indicates that a conversion is done. Supplying
a clock to the Aux_SPI_CLK then outputs data on the
Aux_SPI_DO pin, MSB first.
CONTROLLER
AD986x
An optional auxiliary serial port interface (AuxSPI) can be used to
access an AuxADC. The AuxSPI can initiate an AuxADC conversion
and can be used to retrieve the data. The AuxSPI can be configured
to allow dedicated control of one of the AuxADCs and is available so
that the SPI is not continually busy retrieving AuxADC data.
SPI_CS[x]
SPI_CLK
SPI_CS
SPI_CLK
SPI_SDIO
SPI_DI
03606-0-006
Figure 75. Diagram to Connect 3-Wire SPI to a 4-Wire SPI Controller
Rev. A | Page 28 of 51
AD9861
Data Sheet
Figure 76 shows a timing diagram of the AuxSPI when it is used to control and access an AuxADC.
Figure 77 shows the timing for each of the three AuxADC modes of operation.
1
2 3
AUXSPI_CS
AUXSPI_CLK
AUXSPI_SDO
D
D
D
0
9
8
1. AUXADC CONVERSION START SIGNAL
2. AUXADC CONVERSION DONE
3. AUXADC OUTPUT UDATE (MSB)
03606-0-021
Figure 76. Timing Diagram of AuxSPI
tCONVERSION = tC
NORMAL SPI READOUT
16 SPI CLK
16 SPI CLK
16 SPI CLKs USED TO CONFIGURE AND
INITIATE A START CONVERSION
16 SPI CLKs USED TO READ BACK
8 REGISTER BITS
EXTERNAL START COVERT BIT AND
SPI READOUT MODE
EXTERNAL PIN USED TO INITIATE A
START CONVERSION
16 SPI CLKs USED TO READ BACK
8 REGISTER BITS
READOUT MODE WITH AUXILIARY SPI
EXTERNAL PIN USED TO INITIATE A
START CONVERSION
8-BIT SERIAL
OUTPUT
READOUT MODE WITH
AUXILIARY SPI
CYCLE TIME = tC + 8 SPI CLK
EXTERNAL START COVERT BIT AND
SPI READOUT MODE
CYCLE TIME = tC + 16 SPI CLK
NORMAL SPI READOUT
CYCLE TIME = 16 SPI CLK + tC + 16 SPI CLK
03606-0-007
Figure 77. AuxADC Data Cycle Times for Various Readout Methods
Rev. A | Page 29 of 51
AD9861
Data Sheet
Flexible I/O Interface Options
DIGITAL BLOCK
The AD9861 can accommodate various data interface transfer
options (flexible I/O). The AD9861 uses two 10-bit buses, an
upper bus (U10) and a lower bus (L10), to transfer the dual-
channel 10-bit ADC data and dual-channel 10-bit DAC data by
means of interleaved data, parallel data, or a mix of both. Table 11
shows the different I/O configurations of the modes depending
on half-duplex or full-duplex operation. Table 12 and Table 13
summarize the pin configurations versus the modes.
The AD9861 digital block allows the device to be configured in
various timing and operation modes. The following sections discuss
the flexible I/O interfaces, the clock distribution block, and the
programming of the device through mode pins or SPI registers.
Table 11. Flexible Data Interface Modes
Mode
Concurrent Tx + Rx Mode
Name
Tx Only Mode (Half-Duplex)
Rx Only Mode (Half-Duplex)
(Full-Duplex)
General Notes
AD9861
AD9861
Rx Data Rate
HD20
Tx_A DATA
Rx_A DATA
= 1 × ADC Sample
U[0:9]
Tx_B DATA
L[0:9]
L[0:9]
Rx_B DATA
U[0:9]
Rate
DIGITAL
Tx/Rx
DIGITAL
Tx/Rx
Two 10-Bit Parallel Rx Data
Buses
Tx Data Rate
BACK
END
BACK
END
IFACE1
IFACE2
IFACE3
IFACE1
IFACE2
IFACE3
OUTPUT CLOCK
OUTPUT CLOCK
OUTPUT CLOCK
OUTPUT CLOCK
N/A
= 1 × ADC Sample
Rate
03606-0-008
03606-0-012
Two 10-Bit Parallel Tx Data
Buses
AD9861
AD9861
Rx Data Rate
= 2 × ADC Sample
Rate
One 10-Bit Interleaved Rx
Data Bus
HD10
Tx_A/B DATA
TxSYNC
RxSYNC
Rx_A/B DATA
Tx/Rx
U[0:9]
L[9]
U[9]
L[0:9]
DIGITAL
BACK
END
DIGITAL
BACK
END
Tx/Rx
IFACE1
IFACE2
IFACE3
IFACE1
IFACE2
IFACE3
OUTPUT CLOCK
OUTPUT CLOCK
OUTPUT CLOCK
OUTPUT CLOCK
N/A
Tx Data Rate
= 2 × ADC Sample
Rate
03606-0-009
03606-0-013
One 10-Bit Interleaved Tx
Data Bus
AD9861
AD9861
AD9861
Rx Data Rate
= 2 × ADC Sample
Rate
One 10-Bit Interleaved Rx
Data Bus
Tx Data Rate
= 2 × ADC Sample
Rate
FD
Tx_A/B DATA
Tx_A/B DATA
Rx_A/B DATA
TxSYNC
U[0:9]
L[0:9]
U[0:9]
L[0:9]
U[0:9]
L[0:9]
Rx_A/B DATA
DIGITAL
BACK
END
DIGITAL
BACK
END
DIGITAL
BACK
END
TxSYNC
IFACE1
IFACE2
IFACE3
IFACE1
IFACE2
IFACE3
IFACE1
IFACE2
IFACE3
OUTPUT CLOCK
OUTPUT CLOCK
OUTPUT CLOCK
OUTPUT CLOCK
OUTPUT CLOCK
OUTPUT CLOCK
03606-0-010
03606-0-014
03606-0-016
One 10-Bit Interleaved Tx
Data Bus
AD9861
AD9861
Rx Data Rate
Clone
Tx_A/B DATA
TxSYNC
Rx_A DATA
Rx_B DATA
= 1 × ADC Sample
U[0:9]
L[9]
U[0:9]
L[0:9]
Rate
DIGITAL
BACK
END
DIGITAL
BACK
END
Two 10-Bit Parallel Rx Data
Buses
Tx Data Rate
= 2 × ADC Sample
Rate
Tx/Rx
Tx/Rx
IFACE1
IFACE2
IFACE3
IFACE1
IFACE2
IFACE3
OUTPUT CLOCK
OUTPUT CLOCK
OUTPUT CLOCK
OUTPUT CLOCK
N/A
03606-0-011
03606-0-015
One 10-Bit Interleaved Tx
Data Bus
Requires SPI Interface to
Configure; Similar to AD9860
Data Interface
Rev. A | Page 30 of 51
Data Sheet
AD9861
Table 12 describes AD9861 pin function (when mode pins are used) relative to I/O mode, and for half-duplex modes whether transmitting or
receiving.
Table 12. AD9861 Pin Function vs. Interface Mode (No SPI Cases)
Mode Name
U10
L10
IFACE1
IFACE2
IFACE3
FD
HD10
(Tx/ = High)
Interleaved Tx Data
Interleaved Tx Data
Interleaved Rx Data
MSB = TxSYNC
Others = Three-state
TxSYNC
Buffered Rx Clock
Buffered Tx Clock
Buffered Tx Clock
Rx
20
Tx/ = Tied High 10/ Pin Control Tied High
Rx
HD10
MSB = RxSYNC
Others = Three-state
Interleaved Rx Data
Tx_B Data
Rx
20
Buffered Rx Clock
Buffered Tx Clock
Buffered Rx Clock
Tx/ = Tied Low 10/ Pin Control Tied High
Rx
(Tx/ = Low)
HD20
Tx_A Data
Rx
20
Tx/ = Tied High 10/ Pin Control Tied Low
Rx
(Tx/ = High)
HD20
Rx_B Data
Rx_A Data
Rx
20
Tx/ = Tied Low 10/ Pin Control Tied Low
Rx
(Tx/ = Low)
Clone Mode
Clone mode not available without SPI.
Clone mode not available without SPI.
Rx
(Tx/ = High)
Clone Mode
Rx
(Tx/ = Low)
Table 13 describes AD9861 pin function (when SPI programming is used) relative to flexible I/O mode, and for half-duplex modes whether
transmitting or receiving.
Table 13. AD9861 Pin Function vs. Interface Mode (Configured through the SPI Registers)
Mode Name
U10
L10
IFACE1
IFACE2
IFACE3
FD
Interleaved Tx Data
Interleaved Rx Data
TxSYNC
Buffered System
Clock
Buffered Tx Clock
HD10, Tx Mode
Interleaved Tx Data
MSB = TxSYNC
Others = Three-state
Rx
Tx/ = Tied High
Optional Buffered Buffered Tx Clock
System Clock
Rx
(Tx/ = High)
HD10, Rx Mode
MSB = RxSYNC
Other = Three-state
Interleaved Tx Data
Rx
Tx/ = Tied Low
Optional Buffered Buffered Rx Clock
System Clock
Rx
(Tx/ = Low)
HD20, Tx Mode
Tx_A Data
Tx_B Data
Rx
Tx/ = Tied High
Optional Buffered Buffered Tx Clock
System Clock
Rx
(Tx/ = High)
HD20, Rx Mode
Rx_B Data
Rx_A Data
Rx
Tx/ = Tied Low
Optional Buffered Buffered Rx Clock
System Clock
Rx
(Tx/ = Low)
Clone Mode ,
Tx Mode
Interleaved Tx Data
MSB = TxSYNC
Others = Three-state
Rx
Tx/ = Tied High
Optional Buffered Buffered Tx Clock
System Clock
Rx
(Tx/ = High)
Clone Mode ,
Rx Mode
Rx_B Data
Rx_A Data
Rx
Tx/ = Tied Low
Optional Buffered Buffered Rx Clock
System Clock
Rx
(Tx/ = Low)
Summary of Flexible I/O Modes
The following notes provide a general description of the FD
mode configuration. For more information, refer to Table 16.
FD Mode
Note the following about the Tx path in FD mode:
The full-duplex (FD) mode can be configured by using mode pins or
with SPI programming. Using the SPI allows additional
configuration flexibility of the device.
•
Interpolation rate of 2× or 4× can be programmed with
mode pins or SPI.
FD mode is the only mode that supports full-duplex, receive, and
transmit concurrent operation. The upper 10-bit bus (U10) is used
to accept interleaved Tx data, and the lower 10-bit bus (L10) is used
to output interleaved Rx data. Either the Rx path or the Tx path (or
both) can be independently powered down using either (or both) the
RxPwrDwn and TxPwrDwn pins. FD mode requires interpolation of
2× or 4×.
•
Max DAC update rate = 200 MSPS.
Max Tx input data rate = 80 MSPS/channel (160 MSPS
interleaved).
•
•
TxSYNC is used to direct Tx input data.
TxSYNC = high indicates channel Tx_A data.
TxSYNC = low indicates channel Tx_B data.
Buffered Tx clock output (from IFACE3 pin) equals 2× the
DAC update rate; one rising edge per interleaved Tx sample.
Rev. A | Page 31 of 51
AD9861
Data Sheet
Note the following about the Rx path in FD mode:
HD20 Mode
The half-duplex 20-bit parallel output, HD20, can be configured
using mode pins or through SPI programming.
•
ADC CLK Div register can be used to divide down the clock
driving the ADC, which accepts up to 50 MHz (AD9861-50) or
up to 80 MHz (AD9861-80).
HD20 mode supports half-duplex only operations and can
interface to a single 20-bit data bus (two parallel 10-bit buses).
Both the U10 and L10 buses are used on the AD9861. The logic
•
•
•
Max ADC sampling rate = 50 MSPS (AD9861-50) or 80 MSPS
(AD9861-80).
level of the Tx/ selector (controlled through IFACE1 pin) is
Rx
The Rx path output data rate is 2× the ADC sample rate
(interleaved).
used to configure the buses as Rx outputs (during Rx operation)
or as Tx inputs (during Tx operation). A single pin is used to
output the clocks for Rx and Tx data latching (from the IFACE3
pin) switching, depending on which path is enabled.
Rx_A output when IFACE2 logic level = low.
Rx_B output when IFACE2 logic level = high.
HD10 Mode
The following notes provide a general description of the HD20
mode configuration. For more information, refer to Table 16.
The half-duplex, 10-bit interleaved outputs mode, HD10 can be
configured using mode pins or the SPI.
Note the following about the Tx Path in HD20 mode:
HD10 mode supports half-duplex only operations and can interface
to a single 10-bit data bus with independent Rx and Tx
synchronization pins (RxSYNC and TxSYNC). Both the U10 and
•
Interpolation rate of 1×, 2×, or 4× can be programmed
with mode pins or SPI.
•
Max DAC update rate = 200 MSPS.
L10 buses are used on the AD9861, but the logic level of the Tx/
Rx
Max Tx input data rate = 160 MSPS/channel with bypassed
interpolation filters, 100 MSPS for 2× interpolation or
50 MSPS for 4× interpolation.
selector (controlled through IFACE1 pin) is used to disable and
three-state the unused bus, allowing U10 and L10 to be tied together.
The MSB of the unused bus acts as the RxSYNC (during Rx
operation) or TxSYNC (during Tx operation). A single pin is used to
output the clocks for Rx and Tx data latching (from the IFACE3 pin)
switching, depending on which path is enabled. HD10 mode
requires interpolation of 2× or 4×.
•
Tx_A DAC data is accepted from the U10 bus; Tx_B DAC
data is accepted from the L10 bus.
Note the following about the Rx path in HD20 mode:
•
ADC CLK Div register can be used to divide down the
clock driving the ADC, which accepts up to 50 MHz
(AD9861-50) or up to 80 MHz (AD9861-80).
The following notes provide a general description of the HD10 mode
configuration. For more information, refer to Table 16.
Note the following about the Tx path in HD10 mode:
•
•
Max ADC sampling rate = 50 MSPS (AD9861-50) or
80 MSPS (AD9861-80).
•
•
•
Interpolation rate of 2× or 4× can be programmed with mode
pins or SPI.
The Rx_A output data is output on L10 bus; the Rx_B
output data is output on U10 bus.
Interleaved Tx data accepted on U10 bus, L10 bus MSB acts as
TxSYNC.
Clone Mode
Max DAC update rate = 200 MSPS.
Max Tx input data rate = 80 MSPS/channel (160 MSPS
interleaved).
An interface mode provides a similar interface to the AD9860
when used in half-duplex mode. This mode is referred to as
clone mode and requires SPI to configure.
•
TxSYNC is used to direct Tx input data.
TxSYNC = high indicates channel Tx_A data.
TxSYNC = low indicates channel Tx_B data.
Clone mode provides a parallel Rx data output (20 bits) while in
Rx mode, and accepts interleaved Tx data (10-bit) while in Tx
mode. Both the U10 and L10 buses are used on the AD9861.
The logic level of the Tx/ selector (controlled through the
Rx
Note the following about the Rx path in HD10 mode:
IFACE1 pin) is used to configure the buses for Rx outputs
(during Rx operation) or as Tx inputs (during Tx operation). A
single pin is used to output the clocks for Rx and Tx data
latching (from the IFACE3 pin), depending on which path is
enabled. Clone mode requires interpolation of 2× or 4×.
•
ADC CLK Div register can be used to divide down the clock
driving the ADC, which accepts up to 50 MHz (AD9861-50) or
up to 80 MHz (AD9861-80).
•
Max ADC sampling rate = 50 MSPS (AD9861-50) or 80 MSPS
(AD9861-80).
The following notes provide a general description of the clone
mode configuration. For more information, refer to Table 16.
•
•
•
Output data rate = 2× ADC sample rate.
Interleaved Rx data output from L10 bus.
Note the following about the Tx path in clone mode:
Rx_A output when IFACE2 (or RxSYNC) logic level = low.
Rx_B output when IFACE2 (or RxSYNC) logic level = high.
•
Interpolation rate of 2× or 4× can be programmed with
mode pins or SPI.
Rev. A | Page 32 of 51
Data Sheet
AD9861
Configuring with Mode Pins
•
•
•
Max DAC update rate = 200 MSPS.
Max Tx input data rate = 80 MSPS/channel (160 MSPS
interleaved).
The flexible interface can be configured with or without the SPI,
although more options and flexibility are available when using
the SPI to program the AD9861. Mode pins can be used to
power down sections of the device, reduce overall power consump-
tion, configure the flexible I/O interface, and program the
interpolation setting. The SPI register map, which provides
many more options, is discussed in the Configuring with SPI
section.
TxSYNC is used to direct Tx input data.
TxSYNC = high indicates channel Tx_A data.
TxSYNC = low indicates channel Tx_B data.
Buffered Tx clock output (from IFACE3 pin) uses one rising
edge per interleaved Tx sample.
Note the following about the Rx path in clone mode:
Mode Pins/Power-Up Configuration Options
•
ADC CLK Div register can be used to divide down the clock
driving the ADC, which accepts up to 50 MHz (AD9861-50) or
up to 80 MHz (AD9851-80).
Various options are configurable at power-up through mode
pins, and also through control pins for power-down modes. The
logic value of the configuration mode pins are latched when the
device is brought out of reset (rising edge of
pin names and their functions are shown in Table 14. Table 15
provides a detailed description of the mode pins.
). The mode
•
•
•
Max ADC sampling rate = 50 MSPS (AD9861-50) or 80 MSPS
(AD9861-80).
RESET
Output data rate = ADC sample rate, that is, two 10-bit parallel
outputs per one buffer Rx clock output cycle.
The Rx_A output data is output on L10 bus; the Rx_B output
data is output on U10 bus.
Table 14. Mode Pin Names and Functions
Pin Name
Duration
Function
RxPwrDwn
Permanent
When high, digital clocks to Rx block are disabled. Analog circuitry that require <10 µs to
power up are powered off.
TxPwrDwn
Permanent
When high, digital clocks to Tx block are disabled (PLL remains powered to maintain output
clock with an optional SPI shut off). Analog circuitry that require <10 µs to power up are
powered off.
Tx/Rx (IFACE1)
Permanent only for
HD Flex I/O interface
When high, digital clocks to Tx block are disabled (PLL remains powered to maintain output
clock with an optional SPI shutoff). Tx analog blocks remain powered up unless Tx_PwrDwn is
asserted.
When low, digital clocks to Rx block are disabled. Rx analog circuitry remain powered up unless
Rx_PwrDwn is asserted.
ADC_LO_PWR
Defined at Reset or
Power-Up
When enabled, this bit scales the ADC power-down by 40%.
SPI_Bus_Enable
(SPI_CS)
Defined at Reset or
Power-Up
This function is controlled through the SPI_CS pin. This pin must remain low to maintain mode
pin functionality (the SPI port remains nonfunctional). This pin must be high when coming out
of reset to enable the SPI.
FD/HD
Defined at Reset or
Power-Up
Configures the flex I/O for FD or HD mode. This control applies only if the SPI bus is disabled.
10/20 only valid for
HD mode
Defined at Reset or
Power-Up
If the flex I/O bus is in HD mode, this bit is used to configure parallel or interleaved data mode.
This control applies only if the SPI bus is disabled.
Interp0 and Interp1
Defined at Reset or
Power-Up
The Interp1 and Interp0 bits configure the PLL and the interpolation rate to 1× [00], 2× [01], or
4× [10]. This control applies only if the SPI bus is disabled.
Table 15. Mode Pin Names and Descriptions
Pin Name
Description
ADC_LO_PWR
ADC Low Power Mode Option. ADC_LO_PWR is latched during the rising edge of RESET.
Logic low results in ADC operation at nominal power mode.
Logic high results in ADC consuming 40% less power than the nominal power mode.
FD/HD (SDO)
For Flex I/O Configuration, this control applies only if the SPI bus is disabled. FD/HD (SDO) is latched during the
rising edge of RESET.
Logic low identifies that the DUT flex I/O port will be configured for half-duplex operation.
10/20 (IFACE2) is also latched during the rising edge of RESET to identify interleaved data mode or parallel data
modes.
Logic low indicates that the flex I/O will configure itself for parallel data mode.
Rev. A | Page 33 of 51
AD9861
Data Sheet
Pin Name
Description
Logic high indicates that the flex I/O will configure itself for interleaved data mode.
20
20
For flex I/O Configuration, The 10/ pin control applies only if the SPI bus is disabled and the device is
10/
20
configured for HD mode. 10/ is latched during the rising edge of RESET.
20
10/ (IFACE2) is used to identify interleaved data mode or parallel data modes.
Logic low indicates that the flex I/O will configure itself for HD20 mode.
Logic high indicates that the flex I/O will configure itself for HD10 mode.
SPI_Bus_Enable (SPI_CS) SPI_CS is latched during the rising edge of RESET.
Logic low results in the SPI being disabled and SPI_DIO, SPI_CLK and SPI_SDO act as mode pins.
Logic high results in the SPI being fully operational, and some of the mode pins are disabled.
Interp0 and Interp1
RxPwrDwn
TxPwrDwn
Tx/Rx
Interpolation/PLL Factor Configuration. This control applies only if the SPI bus is disabled.
SPI_DIO (Interp1) and SPI_CLK (Interp0) configure the Tx path for 1× [00], 2× [01], or 4× [10] interpolation and
also enable the PLL of the same multiplication factor.
Power-Down Control. RxPwrDwn logic level controls the power-down function of the Rx path.
Logic low results in the Rx path operating at normal power levels.
Logic high disables the ADC clock and disables some bias circuitry to reduce power consumption.
Power-Down Control. TxPwrDwn logic level controls the power-down function of the Tx path.
Logic low results in the Tx path operating at normal power levels.
Logic high disables the DAC clocks and disables some bias circuitry to reduce power consumption.
Power-Down Control. Tx/Rx pin enables the appropriate Tx or Rx path in the half-duplex mode.
A logic low disables the Tx digital clock and the I/O bus is configured as an output or three-stated.
A logic high disables the Rx digital clocks and the I/O bus is configured as high impedance inputs.
Rev. A | Page 34 of 51
Data Sheet
AD9861
Configuring with SPI
The flexible interface can be configured with register settings. Using the register allows more device programmability. Table 16 shows the
required register writes to configure the AD9861 for FD, optional FD, HD20, optional HD20, HD10, optional HD10, and clone mode. Note
that for modes that use interleaved data buses, enabling 2× or 4× interpolation is required.
Table 16. Registers for Configuring SPI
Register Address
Setting
Description
FD, Mode 1
Register 0x01 [7:5]
Register 0x14 [4]
Register 0x14 [2]
Register 0x13 [1:0]
Optional FD, Mode 2
Register 0x01 [7:5]
Register 0x14 [4]
Register 0x14 [2]
Register 0x13 [1:0]
HD20, Mode 4
[000];
High
High
[01] or [10]
clk_mode—Configures timing mode.
SpiFDnHD—Configures FD mode.
SpiB10n20—Configures FD mode.
Interpolation Control—Configures 2× or 4× interpolation.
[001]
High
High
[01] or [10]
clk_mode—Configures timing mode.
SpiFDnHD—Configures FD mode.
SpiB10n20—Configures FD mode.
Interpolation Control—Configures 2× or 4× interpolation.
Register 0x01 [7:5]
Register 0x14 [4]
Register 0x14 [2]
Register 0x13 [1:0]
Optional HD20, Mode 5
Register 0x01 [7:5]
Register 0x14 [4]
Register 0x14 [2]
Register 0x13 [1:0]
HD10, Mode 7
[000];
Low
Low
[00], [01] or [10]
clk_mode—Configures timing mode.
SpiFDnHD—Configures HD mode.
SpiB10n20—Configures HD20 mode.
Interpolation Control—Configures 1×, 2×, or 4× interpolation.
[011]
Low
Low
[00], [01] or [10]
clk_mode—Configures timing mode.
SpiFDnHD—Configures HD mode.
SpiB10n20—Configures HD20 mode.
Interpolation Control—Configures 1×, 2×, or 4× interpolation.
Register 0x01 [7:5]
Register 0x14 [4]
Register 0x14 [2]
Register 0x13 [1:0]
Optional HD10, Mode 8
Register 0x01 [7:5]
Register 0x14 [4]
Register 0x14 [2]
Register 0x13 [1:0]
Clone, Mode 10
[000]
Low
High
[01] or [10]
clk_mode—Configures timing mode.
SpiFDnHD—Configures HD mode.
SpiB10n20—Configures HD10 mode.
Interpolation Control—Configures 2× or 4× interpolation.
[101]
Low
High
[01] or [10]
clk_mode—Configures timing mode.
SpiFDnHD—Configures HD mode.
SpiB10n20—Configures HD10 mode.
Interpolation Control—Configures 2× or 4× interpolation.
Register 0x01 [7:5]
Register 0x14 [0]
Register 0x13 [1:0]
[111]
High
[01] or [10]
clk_mode—Configures timing mode.
SpiClone—Configures clone mode.
Interpolation Control—Configures 2× or 4× interpolation.
Rev. A | Page 35 of 51
AD9861
Data Sheet
SPI Register Map
Registers 0x00 to 0x29 of the AD9861 provide flexible operation of the device. The SPI allows access to many configurable options. Detailed
descriptions of the bit functions are found in Table 18.
Table 17. Register Map
Reg. Name
Addr
7
6
5
4
3
2
1
0
General
0x00 SDIO BiDir
LSB First
Soft Reset
Clock Mode
0x01 clk_mode[2:0]
Enable IFACE2 Inv clkout
clkout
(IFACE3)
Power-Down
0x02 Tx Analog
TxDigital
RxDigital
PLL Power-
Down
PLL Output
Disconnect
RxA Power-Down 0x03 Rx_A Analog
RxB Power-Down 0x04 Rx_B Analog
Rx Power-Down 0x05 Rx Analog Bias
Rx_A DC Bias
Rx_B DC Bias
RxRef
DiffRef
VREF
Rx Path
Rx Path
Rx Path
Rx path
Rx Path
0x06
0x07
0x08
0x09
0x0A
Rx_A Twos
Complement
Rx_A Clk
Duty
Rx_B Twos
Complement
Rx_B Clk
Duty
Rx Ultralow Rx Ultralow
Power Control Power Control
Rx Ultralow
Power Control
Rx Ultralow
Power Control
Rx Ultralow
Power Control
Rx Ultralow
Power Control
Rx Ultralow
Power Control
Rx Ultralow
Power Control
Tx Path
Tx Path
0B
0C
DAC A Offset [9:2]
DAC A Offset [1:0]
DAC A Offset
Direction
Tx Path
Tx Path
Tx Path
0D
0E
0F
DAC A Coarse Gain Control
DAC B Offset [9:2]
DAC A Fine Gain [5:0]
DAC B Fine Gain [5:0]
DAC B Offset [1:0]
DAC B Offset
Direction
Tx Path
Tx Path
Tx Path
10
11
12
DAC B Coarse Gain Control
TxPGA Gain [7:0]
TxPGA Slave
TxPGA Fast
Enable
Update
I/O Configuration 13
I/O Configuration 14
Tx Twos
Complement
Rx Twos
Complement
Tx Inverse
Sample
Interpolation Control [1:0]
SPI IO Control SpiClone
Dig Loop On
SpiFDnHD
Alt Timing Mode
SpiTxnRx
PLL Div5
SpiB10n20
Clock
Clock
15
16
17
PLL Bypass
ADC Clock Div
PLL to IFACE2
AuxDAC B FS [1:0]
PLL Multiplier [2:0]
PLL Slow
Auxiliary
AuxDAC A FS [1:0]
AuxDAC C FS [1:0]
AuxADC Ref AuxADC Ref
Enable FS
Converters
AuxADC
18
19
Start Average
AuxADC A
Number of AuxADC A Samples [2:0]
AuxADC
Start Average
AuxADC B
Number of AuxADC B Samples [2:0]
AuxADC
AuxADC
AuxADC
AuxADC
AuxADC
AuxADC
AuxADC
AuxADC
AuxDAC
1A
1B
1C
1D
1E
1F
22
23
24
25
26
28
29
AuxADC A2 [1:0]
AuxADC A2 [9:2]
AuxADC A1 [1:0]
AuxADC A1 [9:2]
AuxADC B [1:0]
AuxADC B [9:2]
AuxSPI Enable
Sel 2not1
Refsel B
Start B
Refsel A
Select A
Start A
AuxADC Clock Div[1:0]
AuxDAC A [7:0]
AuxDAC B [7:0]
AuxDAC C [7:0]
Slave Enable
Update C
Update B
Update A
AuxDAC C Sync AuxDAC B Sync AuxDAC A Sync
TxPwrDwn TxPwrDwn TxPwrDwn
Power-Up C Power-Up B Power-Up A
Rev. A | Page 36 of 51
Data Sheet
AD9861
Table 18. Register Bit Descriptions
Register Bit
Description
Register 0: General
Bit 7: SDIO BiDir (Bidirectional)
Default setting is low, which indicates that the SPI serial port uses dedicated input and output lines (4-
wire interface), SDIO and SDO pins, respectively. Setting this bit high configures the serial port to use
the SDIO pin as a bidirectional data pin.
Bit 6: LSB First
Default setting is low, which indicates MSB first SPI port access mode. Setting this bit high configures
the SPI port access to LSB first mode.
Bit 5: Soft Reset
Writing a high to this register resets all the registers to their default values and forces the PLL to relock
to the input clock. The soft reset bit is a one-shot register, and is cleared immediately after the register
write is completed.
Register 1: Clock Mode
Bits 7–5: Clk Mode
These bits represent the clocking interface for the various modes. Setting 000 is default. Setting 111 is
used for clone mode. Refer to the Summary of Flexible I/O Modes section for definition of clone mode.
Setting
000
001
Mode
Standard FD, HD10, HD20 Clock (Modes 1, 4, 7)
Optional FD timing (Mode 2)
Not Used
010
011
100
Optional HD20 timing (Mode 5)
Not Used
101
110
Optional HD10 timing (Mode 8)
Not Used
111
Clone Mode (Mode 10)
Bit 2: Enable IFACE2 clkout
Enables the IFACE2 port to be an output clock. Also inverts the IFACE2 output clock in full-duplex
mode.
Bit 1: Inv clkout (IFACE3)
Register 2: Power-Down
Invert the output clock on IFACE3.
Bits 7–5: Tx Analog (Power-Down)
Three options are available to reduce analog power consumption for the Tx channels. The first two
options disable the analog output from Tx Channel A or B independently, and the third option disables
the output of both channels and reduces the power consumption of some of the additional analog
support circuitry for maximum power savings. With all three options, the DAC bias current is not
powered down so recovery times are fast (typically a few clock cycles). The list below explains the
different modes and settings used to configure them.
Power-Down Option Bits Setting [7:5]
Power-Down Tx A Channel Analog Output [1 0 0]
Power-Down Tx B Channel Analog Output [0 1 0]
Power-Down Tx A and Tx B Analog Outputs [1 1 1]
Bit 4: Tx Digital (Power-Down)
Default setting is low, which enables the transmit path digital to operate as programmed through
other registers. By setting this bit high, the digital blocks are not clocked to reduce power
consumption. When enabled, the Tx outputs are static, holding their last update values.
Bit 3: Rx Digital (Power-Down)
Bit 2: PLL Power-Down
Setting this bit high powers down the digital section of the receive path of the chip. Typically, any
unused digital blocks are automatically powered down.
Setting this register bit high forces the CLKIN multiplier to a power-down state. This mode can be used
to conserve power or to bypass the internal PLL. To operate the AD9861 when the PLL is bypassed, an
external clock equal to the fastest on-chip clock is supplied to the CLKIN.
Bit 1: PLL Output Disconnect
Register 3/4: Rx Power-Down
Setting this register bit high disconnects the PLL output from the clock path. If the PLL is enabled, it
locks or stays locked as normal.
Bit 7: Rx_A Analog/
Rx_B Analog (Power-Down)
Either ADC or both ADCs can be powered down by setting the appropriate register bit high. The entire
analog circuitry of Rx channel is powered down, including the differential references, input buffer, and
the internal digital block. The band gap reference remains active for quick recovery.
Bit 6: Rx_A DC Bias/
Rx_B DC Bias (Power-Down)
Setting either of these bits high powers down the input common-mode bias network for the respective
channel and requires an input signal to be properly dc-biased. By default, these bits are low, and the Rx
inputs are self-biased to approximately AVDD/2 and accept an ac-coupled input.
Register 5: Rx Power-Down
Bit 7: Rx Analog Bias (Power-
Down)
Setting this bit high powers down all analog bias circuits related to the receive path (including the
differential reference buffer). Because bias circuits are powered down, an additional power saving, but
also a longer recovery time relative to other Rx power-down options, will result.
Bit 6: RxREF (Power-Down)
Setting this register bit high powers down internal ADC reference circuits. Powering down these
Rev. A | Page 37 of 51
AD9861
Data Sheet
Register Bit
Description
circuits provides additional power saving over other power-down modes. The Rx path wake-up time
depends on the recovery of these references typically of the order of a few milliseconds.
Bit 5: DiffRef (Power-Down)
Setting this bit high powers down the ADC’s differential references, REFT and REFB. Recovery time
depends on the value of the REFT and REFB decoupling capacitors.
Bit 4: VREF (Power-Down)
Setting this register bit high powers down the ADC reference circuit, VREF. Powering down the Rx band
gap reference allows an external reference to drive the VREF pin setting full-scale range of the Rx paths.
Registers 6/7: Rx Path
Bit 5: Rx_A Twos Complement/
Rx_B Twos Complement
Default data format for the Rx data is straight binary. Setting this bit high generates twos complement
data.
Bit 4: Rx_A Clk Duty/Rx_B Clk Duty Setting either of these bits high enables the respective channels on-chip duty cycle stabilizer (DCS)
circuit to generate the internal clock for the Rx block. This option is useful for adjusting for high speed
input clocks with skewed duty cycle. The DCS mode can be used with ADC sampling frequencies over
40 MHz.
Registers 8/9/A: Rx Path
Rx Ultralow Power Control Bits
Set all bits high, in combination with asserting the ADC_LO_PWR pin, to reduce the power
consumption of the Rx path by a fourth of normal Rx path power consumption.
Registers 0B/0C/0E/0F: Tx Path
DAC A/DAC B Offset
These 10-bit, twos complement registers control a dc current offset that is combined with the Tx A or Tx
B output signal. An offset current of up to 12% IOUTFS (2.4 mA for a 20 mA full-scale output) can be
applied to either differential pin on each channel. The offset current can be used to compensate for
offsets that are present in an external mixer stage, reducing LO leakage at its output. The default
setting is 0x00, no offset current. The offset current magnitude is set by using the lower nine bits.
Setting the MSB high adds the offset current to the selected differential pin, while an MSB low setting
subtracts the offset value.
DAC A/DAC B Offset Direction
Registers 0D/10: Tx Path
This bit determines to which of the differential output pins for the selected channel the offset current is
applied. Setting this bit low applies the offset to the negative differential pin. Setting this bit high
applies the offset to the positive differential pin.
Bits 7, 6: DAC A/DAC B Coarse Gain These register bits scale the full-scale output current (IOUTFS) of either Tx channel independently. IOUT of
Control
the Tx channels is a function of the RSET resistor, the TxPGA setting, and the coarse gain control setting.
00
01
10
11
Output current scaling by 1/11
Output current scaling by ½
No output current scaling
No output current scaling
Bits 5–0: DAC A/DAC B Fine Gain
MSB, LSB
The DAC output curve can be adjusted fractionally through the gain trim control. Gain trim of up to
4% can be achieved on each channel individually. The gain trim register bits are a twos complement
attention control word.
100000
111111
000000
000001
011111
Maximum positive gain adjustment
Minimum positive gain adjustment
No adjustment (default)
Minimum negative gain adjustment
Maximum negative gain adjustment
Register 11: Tx Path
Bits 0–7: TxPGA Gain
This 8-bit, straight binary (Bit 0 is the LSB, Bit 7 is the MSB) register controls for the Tx programmable gain
amplifier (TxPGA). The TxPGA provides a 20 dB continuous gain range with 0.1 dB steps (linear in dB)
simultaneously to both Tx channels. By default, this register setting is 0xFF.
MSB, LSB
0000 0000
1111 1111
Minimum gain scaling –20 dB
Maximum gain scaling 0 dB
Register 12: Tx Path
Bit 6: TxPGA Slave Enable
The TxPGA gain is controlled through register TxPGA gain setting and, by default, is updated
immediately after the register write. If this bit is set, the TxPGA gain update is synchronized with the
falling edge of a signal applied to the TxPwrDwn pin and is enabled during the wake-up from power-
down.
Rev. A | Page 38 of 51
Data Sheet
AD9861
Register Bit
Description
Bit 4: TxPGA Fast Update (Mode)
The TxPGA fast bit controls the update speed of the TxPGA. When fast update mode is enabled, the
TxPGA provides fast gain settling within a few clock cycles, which may introduce spurious signals at the
output of the Tx path. The default setting for this bit is low, and the TxPGA gives a smooth transition
between gain settings. Fast mode is enabled when this bit is set high.
Register 13: I/O Configuration
Bit 7: Tx Twos Complement
The default data format for Tx data is straight binary. Set this bit high when providing twos
complement Tx data.
Bit 6: Rx Twos Complement
Bit 5: Tx Inverse Sample
The default data format for Rx data is straight binary. Set this bit high when providing twos
complement Rx data.
By default, the transmit data is sampled on the rising edge of the CLKOUT. Setting this bit high changes
this, and the transmit data is sampled on the falling edge.
Bits 1,0: Interpolation Control
These register bits control the interpolation rate of the transmit path. The default settings are both bits
low, indicating that both interpolation filters are bypassed. The MSB and LSB are Address Bits 1 and 0,
respectively. Setting binary 01 provides an interpolation rate of 2×; binary 10 provides an interpolation
rate of 4×.
Register 14: I/O Configuration
Bit 5: Dig Loop On
When enabled, this bit enables a digital loop back mode. The digital loop-back mode provides a means
of testing digital interfaces and functionality at the system level. In digital loop-back mode, the full-
duplex interface must be enabled. (Refer to the Flexible I/O Interface Options section.) The device
accepts digital input from the bus according to the FD mode timing and uses the Tx digital path (with
enabled interpolation and other digital settings); the processed data is then output from the Rx path
bus.
Bit 4: SPI_FDnHD
Bit 3: SpiTxnRx
Control bit to configure full-duplex (high) or half-duplex (low) interface mode. This register, in
combination with the SpiB10n20 register, configures the interface mode of FD, HD10, or HD20. The
register setting is ignored for clone mode operation. By default, this register is set high, and the device
is in FD mode.
Control bit used for toggling between transmit or receive mode for the half-duplex clock modes. High
represents Tx and low represents Rx.
Bit 2: SpiB10n20
Bit 1: SPI IO Control
Bit 0: SpiClone
Control bit for 10-bit or 20-bit modes. High represents 10-bit mode and Low represents 20-bit mode.
Use in conjunction with SpiTxnRx [Register14, Bit 3] to override external TxnRx pin operation.
Set high when in clone mode (see the Flexible I/O Interface Options section for definition of clone
mode). Clk_mode must also be set to binary 111, i.e., [Register 01[7:5] = 111.
Register 15: Clock
Bit 7: PLL_Bypass
Bits 5: ADC Clock Div
Setting this bit high bypasses the PLL. When bypassed, the PLL remains active.
By default, the ADCs are driven directly from CLKIN in normal timing operation or from the PLL output
clock in the alternative timing operation. This bit is used to divide the source of the ADC clock prior to
the ADCs. The default setting is low and performs no division. Setting this bit high divides the clock by
2.
Bit 4: Alt Timing Mode
The timing table in the data sheet describes two timing modes: the normal timing operation mode and
the alternative timing operation mode. The default configuration is normal timing mode and the CLKIN
drives the Rx path. In alternative timing mode, the PLL output is used to drive the Rx path. The
alternative operation mode is configured by setting this bit high.
Bit 3: PLL Div5
The output of the PLL can be divided by 5 by setting this bit high. By default, the PLL directly drives the
Tx digital path with no division of its output.
Bits 2–0: PLL Multiplier
These bits control the PLL multiplication factor. A default setting is binary 000, which configures the
PLL to 1× multiplication factor. This register, in combination with the PLL Div5 register, sets the PLL
output frequency. The programmable multiplication factors are
000
1×
001
2×
010
4×
011
8×
100
101 – 111
16×
not used
Register 16: Clock
Bit 5: PLL to IFACE2
Setting this bit high switches the IFACE2 output signal to the PLL output clock. It is valid only if Register
0x01, Bit 2 is enabled or if full-duplex mode is configured.
Bit 2: PLL Slow
Changes the PLL loop bandwidth and changes the profile of the phase noise generated from the PLL
clock.
Rev. A | Page 39 of 51
AD9861
Data Sheet
Register Bit
Description
Register 17: Auxiliary Converters
Bits 7–2: AuxDAC A FS/AuxDAC B
FS/AuxDAC C FS
These register bits independently scale the full-scale output voltage for the AuxDACs. If the full-scale
voltage is programmed to a value greater than PLL_VDD – 0.2 V, the AuxDAC becomes nonlinear in this
region.
MSB, LSB
AuxDAC Full-Scale Output Voltage
00
01
10
11
3.0 V
3.3 V
2.5 V
2.7 V
Bit 1: AuxADC Ref Enable
Bit 0: AuxADC Ref FS
This bit enables the on-chip, supply independent reference for the AuxADC. By default, the AuxADC
uses the PLL_AVDD supply for its full-scale voltage level.
When the AuxADC Ref Enable bit is set high, this bit allows the user to select the full-scale value of the
AuxADC. A low setting sets the full-scale value to 3.0 V; a high setting sets the full-scale value to 2.5 V. If
the full-scale voltage is programmed to a value greater than PLL_VDD – 0.2 V, the AuxADC is not linear
in this region.
Registers 18/19 : AuxADC
Bit 7: Start Average AuxADC A/
Start Average AuxADC B
These registers are used to initiate a conversion cycle of the AuxADCs for a number of consecutive
samples and then report the average result. The number of consecutive samples is programmed in the
number of AuxADC A/AuxADCB samples register. The external pin Aux_SPI_CS can be configured to
allow it to initiate the start average conversion cycle. The result is placed in the appropriate register
corresponding to the AuxADC output [Registers 0x1A to 0x21].
Bit 7: Number of AuxADC A/
AuxADC B Samples
These bits control the number of samples that the AuxADC collects and uses to calculate an average
value. This register is used in conjunction with the start average AuxADC register.
MSB, LSB
000
Number of Samples to Average
1
001
2
010
4
011
8
100
16
101
32
110
64
111
Not Used
Registers 1A–21: AuxADC
These 10-bit, offset binary registers are read-only and store the last corresponding AuxADC output
values. The AD9861 has two AuxADC SAR converters: AuxADC A and AuxADC B. AuxADC A has a
multiplexed input, which allows the user to select either input by using the Select A register. The 10 bits
are broken into two registers, one containing the upper eight bits and the other containing the lower
two bits.
Register 22: AuxADC
Bit 7: AuxSPI (Enable)
Bit 6: Sel 2not1
Enables the AuxSPI, which can be used to initiate a conversion and read back one of the AuxADCs.
If the auxiliary serial port is used, this bit selects which AuxADC, 1 or 2, uses the dedicated auxiliary
serial port. By default (low setting), the auxiliary serial port controls AuxADC A. Setting this bit high
allows the auxiliary serial port to control AuxADC B.
Bits 5, 2: Refsel B/A
By default, the AuxADCs use an external reference applied to the AUX_REF pin. This voltage acts as the
full-scale reference for the selected AuxADC. Either AuxADC can use an internally generated reference,
which can be a buffered version of the analog supply voltage or a supply independent, 3.0 V or 2.5 V
internal reference. To enable use of the internal reference for either of the AuxADCs, set the respective
Refsel register high. For internal reference configuration, see Register 17.
Bit 1: Select A
This bit is used to select which of the two inputs is connected to the AuxADC. By default (setting low),
the AUX_ADC_A2 (Aux2 pin) is connected to AuxADC A. Setting the respective bit high connects the
AUX_ADC_A1 (Aux1 pin) to AuxADC A.
Bit 3, 0: Start B/A
Setting either of these bits to high initiates a conversion of the respective AuxADC, A or B. The register
bit always reads back a low.
Rev. A | Page 40 of 51
Data Sheet
AD9861
Register Bit
Description
Register 23: AuxADC
Bits 1,0: AuxADC Clock Div
The AuxADCs clock can be based on either the clock driving the Rx ADC, or it can be driven from the
SPI_CLK. The conversion rate of the AuxADCs must be less than 40 MHz. In order to facilitate a slower
speed clock for the AuxADC, these bits are used to divide down the Rx ADC clock prior to driving the
AuxADC. The following options are programmable through this register:
MSB, LSB
AuxADC Sampling Rate
Rx ADC Clock/4
Rx ADC Clock/2
Rx ADC Clock
SPI_CLK drives AuxADC
00
01
10
11
Registers 24, 25, 26: AuxDAC
AuxDAC A, B, and C Output
Control Word
Three 8-bit, straight binary words are used to control the output of three on-chip AuxDACs. The
AuxDAC output changes take effect immediately after any of the serial writes are completed. The DAC
output control words have default values of 0. The smaller programmed output controlled words
correspond to lower DAC output levels.
Register 28: AuxDAC
Bit 7: Slave Enable
A low setting (default) updates the AuxDACs after the respective register is written to. To synchronize
the AuxDAC outputs to each other, a slave mode can be enabled by setting this bit high and then
setting the appropriate update registers high.
Bits 2/1/0: Update C, B, and A
Setting a high bit to any of these bits initiates an update of the respective AuxDAC, A, B or C, when
slave mode is enabled using the slave enable register. The register bit is a one-shot and always reads
back a low. Be sure to keep the slave enable bit high when using the AuxDAC synchronization option.
Register 29: AuxDAC
Bits 7/6/5: AuxDAC C/B/A Sync
TxPwrDwn
Setting any of these bits high synchronizes AuxDAC updates only when the TxPwrDwn rising edge
occurs. This syncronizes the AuxDAC update to the Tx path power-up.
Bits 2/1/0: Power Up C, B, and A
Setting any of these bits high powers up the appropriate AuxDAC. By default, these bits are low and the
AuxDACs are disabled.
Rev. A | Page 41 of 51
AD9861
Data Sheet
PROGRAMMABLE REGISTERS
The AD9861 contains internal registers that are used to configure the
device. A serial port interface provides read/write access to the
internal registers. Single-byte or dual-byte transfers are supported as
well as MSB first or LSB first transfer formats. The AD9861’s serial
interface port can be configured as a single pin I/O (SDIO) or as two
unidirectional pins for in/out (SDIO/SDO). The serial port is a
flexible, serial communications port, allowing easy interface to many
industry-standard microcontrollers and microprocessors.
Normally, using one communication cycle in a multibyte
transfer is the preferred method; however, single byte
communication cycles are useful to reduce CPU overhead when
register access requires only one byte. An example of this is to
write the AD9861 power-down bits.
All data input to the AD9861 is registered on the rising edge of
SCLK. All data is driven out of the AD9861 on the falling edge
of SCLK.
General Operation of the Serial Interface
Instruction Byte
By default, the serial port accepts data in MSB first mode and uses
four pins: SEN, SCLK, SDIO, and SDO by default. SEN is a serial
clock enable pin; SCLK is the serial clock pin; SDIO is a bidirectional
data line; and SDO is a serial output pin.
The instruction byte contains the information shown in
Table 19, and the bits are described in detail after the table.
Table 19. Instruction Byte
MSB
R/nW
D6
2/n1
Byte
D5
A5
D4
A4
D3
A3
D2
A2
D1
A1
LSB
A0
SEN is an active low control gating read and write cycles. When SEN
is high, SDO and SDIO go into a high impedance state.
SCLK is used to synchronize SPI read and writes at a maximum bit
rate of 30 MHz. Input data is registered on the rising edge, and
output data transitions are registered on the falling edge. During
write operations, the registers are updated after the 16th rising clock
edge (and 24th rising clock edge for the dual-byte case). Incomplete
write operations are ignored.
R/nW—Bit 7 of the instruction byte determines whether a read
or write data transfer will occur after the instruction byte write.
Logic high indicates a read operation. Logic low indicates a
write operation.
2/n1 Byte—Bit 6 of the instruction byte determines the number
of bytes to be transferred during the data transfer cycle of the
communication cycle. Logic high indicates a 2-byte transfer.
Logic low indicates a 1-byte transfer.
SDIO is an input data only pin by default. Optionally, a 3-pin
interface may be configured using the SDIO for both input and
output operations and three-stating the SDO pin. Refer to the SDIO
BiDir bit in Register 0x00 (Table 18).
A5, A4, A3, A2, A1, A0—Bits 5, 4, 3, 2, 1, and 0 of the
instruction byte determine which register is accessed during the
data transfer portion of the communication cycle. For 2-byte
transfers, this address is the starting byte address. The second
byte address is automatically decremented when the interface is
configured for MSB first transfers. For LSB first transfers, the
address of the second byte is automatically incremented.
SDO is a serial output data pin used for readback operations in 4-
wire mode and is three-stated when SDIO is configured for
bidirectional operation.
There are two phases to a communication cycle with the AD9861.
Phase 1 is the instruction cycle, which is the writing of an
instruction byte into the AD9861, coincident with the first eight
SCLK rising edges. The instruction byte provides the AD9861 serial
port controller with information regarding the data transfer cycle,
which is Phase 2 of the communication cycle. The Phase 1
instruction byte defines whether the upcoming data transfer is read
or write, the number of bytes in the data transfer (one or two), and
the starting register address for the first byte of the data transfer.
Table 20. Serial Port Interface Timing
Maximum SCLK Frequency (fSCLK
Minimum SCLK High Pulse Width (tPWH
Minimum SCLK Low Pulse Width (tPWL
Maximum Clock Rise/Fall Time
)
40 MHz
12.5 ns
12.5 ns
1 ms
)
)
Data to SCLK timing (tDS
Data Hold Time (tDH
)
12.5 ns
0 ns
)
The first eight SCLK rising edges of each communication cycle are
used to write the instruction byte into the AD9861. The remaining
SCLK edges are for Phase 2 of the communication cycle. Phase 2 is
the actual data transfer between the AD9861 and the system
controller. Phase 2 of the communication cycle is a transfer of one or
two data bytes as determined by the instruction byte.
Rev. A | Page 42 of 51
Data Sheet
AD9861
Write Operations
The SPI write operation uses the instruction header to configure a 1-
byte or 2-byte register write using the 2/n1 byte setting. The
instruction byte followed by the register data is written serially into
the device through the SDIO pin on rising edges of the interface
clock, SCLK. The data can be transferred MSB first or LSB first
depending on the setting of the LSB first register bit. The write
operation is the same regardless of SDIO BiDir register setting.
Figure 78 to Figure 80 are examples of writing data into the
device. Figure 78 shows a 1-byte write with MSB first; Figure 79
shows a 2-byte write with MSB first; and Figure 80 shows a
2-byte write with LSB first. Note the differences between LSB
and MSB first modes: both the instruction header and data are
reversed, and the second data byte register location is different.
In the default MSB first mode, the second data byte is written to
a decremented register address. In LSB first mode, the second
data byte is written to an incremented register address.
tH
tDS
tHI
tCLK
tDH
tS
tLO
SEN
SCLK
SDIO
DON'T CARE
DON'T CARE
DON'T CARE
R/W
2/1
A5
A4
A3
A2
A1
A0
D7
D6
D5
D4
D3
D2
D1
D0
DON'T CARE
INSTRUCTION HEADER
REGISTER DATA
03606-0-022
Figure 78. 1-Byte Serial Register Write in MSB First Mode
tHI
tLO
tH
tS
tDH
tDS
tCLK
SEN
SCLK
SDIO
DON'T CARE
DON'T CARE
DON'T CARE
DON'T CARE
R/W 2/1 A5 A4 A3 A2 A1 A0 D7 D6 D5 D4 D3 D2 D1 D0 D7 D6 D5 D4 D3 D2 D1 D0
INSTRUCTION HEADER (REGISTER N) REGISTER (N) DATA REGISTER (N–1) DATA
03606-0-023
Figure 79. 2-Byte Serial Register Write in MSB First Mode
tHI
tS
tH
tLO
tDS
tDH
tCLK
SEN
DON'T CARE
DON'T CARE
DON'T CARE
SCLK
SDIO
DON'T CARE
A0 A1 A2 A3 A4 A5 2/1 R/W D0 D1 D2 D3 D4 D5 D6 D7 D0 D1 D2 D3 D4 D5 D6 D7
INSTRUCTION HEADER (REGISTER N) REGISTER (N) DATA REGISTER (N+1) DATA
03606-0-024
Figure 80. 2-Byte Serial Register Write in LSB First Mode
Rev. A | Page 43 of 51
AD9861
Data Sheet
Read Operation
The readback of registers can be a single or dual data byte operation.
The readback can be configured to use 3-wire or
4-wire and can be formatted with MSB first or LSB first. The
instruction header is written to the device either MSB or LSB first
(depending on the mode) followed by the 8-bit output data
(appropriately MSB or LSB justified). By default, the output data is
sent to the dedicated output pin (SDO).
Three-wire operation can be configured by setting the SDIO
BiDir register. In 3-wire mode, the SDIO pin becomes an output
pin after receiving the 8-bit instruction header with a readback
request.
Figure 81 shows a 4-wire SPI read with MSB first; Figure 82
shows a 3-wire read with MSB first; and Figure 83 shows a
4-wire read with LSB first.
tHI
tLO
tS
tCLK
tH
tDS
tDH
tDV
SEN
DON'T CARE
DON'T CARE
DON'T CARE
DON'T CARE
SCLK
SDIO
SDO
R/W
2/1
A5
INSTRUCTION HEADER
DON'T CARE
A4
A3
A2
A1
A0
DON'T CARE
D7
D6
D5
D4
D3
D2
D1
D0
OUTPUT REGISTER DATA
03606-0-025
Figure 81. 1-Byte Serial Register Readback In MSB First Mode, SDIO BiDir Bit Set Logic Low (Default, 4-Wire Mode)
tHI
tLO
tS
tCLK
tH
tDS
tDH
tDV
SEN
DON'T CARE
DON'T CARE
SCLK DON'T CARE
SDIO DON'T CARE
D7
D6
D5
D4
D3
D2
D1
D0
R/W
2/1
A5
A4
A3
A2
A1
A0
INSTRUCTION HEADER
OUTPUT REGISTER DATA
03606-0-026
Figure 82. 1-Byte Serial Register Readback in MSB First Mode, SDIO BiDir Bit Set Logic High (Default, 3-Wire Mode)
tHI
tLO
tS
tCLK
tH
tDS
tDH
tDV
SEN
SCLK
SDIO
DON'T CARE
DON'T CARE
DON'T CARE
DON'T CARE
A0
A1
A2
A3
A4
A5
2/1
R/W
INSTRUCTION HEADER
SDO
DON'T CARE
D0
D1
D2
D3
D4
D5
D6
D7
DON'T CARE
OUTPUT REGISTER DATA
03606-0-027
Figure 83. 1-Byte Serial Register Readback in LSB First Mode, SDIO BiDir Bit Set Logic Low (Default, 4-Wire Mode)
Rev. A | Page 44 of 51
Data Sheet
AD9861
Table 21. PLL Input and Output Minimum and Maximum
Clock Rates
CLOCK DISTRIBUTION BLOCK
Theory/Description
Input Clock
(Min/Max) (MHz)
Output Clock
(Min/Max) (MHz)
The AD9861 uses a clock distribution block to distribute the timing
derived from the input clock (applied to the CLKIN pin, referred to
here as CLKIN) to the Rx and Tx paths. There are many options for
configuring the clock distribution block, which are available through
internal register settings. The Clock Distribution Block Diagram
section describes the timing block diagram breakdown, followed by
the data timing for the different data interface options.
PLL Setting
1× (PLL Bypassed)
1× (PLL Enabled)
2×
4×
8×
* 1/5 ×
* 2/5 ×
* 4/5 ×
* 8/5 ×
1/200
1/200
32/200
16/100
16/50
32/200
32/200
64/200
128/200
6.4/40
16/25
32/200
16/175
16/87.5
16/43.75
16/21.875
The clock distribution block contains a PLL, which includes an
optional output divide-by-5 circuit, an ADC divide-by-2 circuit,
multiplexers, and other digital logic.
6.4/70
12.8/70
25.6/70
51.2/70
* 16/5 ×
There are two main methods of configuring the Rx path timing of
the AD9861, normal timing mode and alternative timing mode,
which are controlled through register Alt timing mode [Register
0x15, Bit 4]. In normal timing mode, the Rx path clock is driven
directly from the CLKIN input and the Tx path is driven by a clock
derived from CLKIN multiplied by the on chip PLL. In alternative
timing mode, the input clock is applied to the PLL circuitry, and the
PLL output clock drives both the Rx path clock and Tx path clock.
* Indicates PLL output divide-by-5 circuit enabled.
Clock Distribution Block Diagram
The Clock Distribution Block diagram is shown in Figure 84.
An output clock formatter configures the output synchroniza-
tion signals, IFACE1, IFACE2, and IFACE3. These interface pin
signals depend on clock mode setting, data I/O configuration,
and other operational settings. Clock mode and data I/O
configuration are defined in register settings of clk_mode,
SpiFDnHD, and SpiB10n20.
Because alternative timing mode uses the PLL to derive the Rx path
clock, the ADC performance may degrade slightly. This degradation
is due to the phase noise from the PLL. Typically it occurs in
undersampling applications when the input signal is above the first
Nyquist zone of the ADC.
Table 22 shows the configuration of the IFACE1, IFACE2 and
IFACE3 pins relative to clock mode (for half-duplex cases, the
IFACE1 pin is an input that identifies if the device is in Rx or Tx
operation mode). The clock mode is used to specify the timing
for each data interface operation modes, which are discussed in
detail in the Flexible I/O Interface Options section. The T and R
extensions after the half-duplex Modes 4, 5, 7, 8, and 10 in the
Table 22 indicate that the device is in transmit or receive
operation mode. The default clock mode setting [Register 0x01,
Bits 5–7, clk_mode] of ‘000’ configures clock Mode 1 for the
full-duplex operation, Mode 4 for half-duplex 20 operation and
Mode 7 for half-duplex 10 operation. Modes 2, 5, 8, and 10 are
optional timing configurations for the AD9861 that can be
programmed through Register 0x01 clk_mode.
The PLL can provide 1×, 2×, 4×, 8×, and 16× multiplication or can be
bypassed and powered down through register PLL bypass [Register
0x15, Bit 7] and through register PLL power-down [Register 0x2, Bit 2].
The PLL requires a minimum input clock frequency of 16 MHz and
needs to provide a minimum PLL output clock of 32 MHz. This limit
applies to the PLL output prior to the optional divide-by-5 circuitry. For
clock frequencies below these limits, the PLL must be bypassed. The
PLL maximum output frequency before the divide-by-5 circuitry is 350
MHz. Table 21 shows the input and output clock rates for all the
multiplication settings.
Rev. A | Page 45 of 51
AD9861
Data Sheet
80MHz MAX
1, 2
4
CLKIN
Rx
PATH
Rx
DIGITAL
BLOCK
IFACE2
IFACE3
1
OUTPUT
CLOCK
FORMATTER
1, 2, 4, 8, 16
1, 5
Tx
PATH
Tx
DIGITAL
BLOCK
3
5
6
2
1. ALTERNATE TIMING MODE: REG 0x15, BIT 4
2. PLL MULTIPLICATION SETTING: REG 0x15, BITS 2–0
3. PLL OUTPUT DIVIDE BY 5; REG 0x15, BIT 3
4. Rx PATH DIVIDE BY 2: REG 0x15, BIT 5
5. PLL BYPASS PATH: REG 0x15, BIT 7
6. INTERP CONTROL, Tx/Rx INV IFACE3, CLK MODE, INV IFACE2, FD/HD, 10/20
Figure 84. Clock Distribution Block Diagram
Table 22. Interface Pins (IFACE1, IFACE2, IFACE3) Configuration Definition for Flexible Interface Operation
Clock
Mode
1
2
4T
4R
5T
5R
7T
7R
8T
8R
10T
10R
PIN
Full-Duplex
TxSync
Half-Duplex, 20-Bit
Rx
Half-Duplex, 10-Bit
Rx
Clone Mode
Rx
IFACE1
IFACE2
IFACE3
Tx/
Tx/
Optional CLKOUT
Tx/
Optional CLKOUT
Buff_CLKIN RxSync Optional CLKOUT
Tx Clock
Tx
Rx
Tx
Rx
Tx
Rx
Tx
Rx
Tx
Rx
Clock
Clock
Clock
Clock
Clock
Clock
Clock
Clock
Clock
Clock
The Tx clock output frequency depends on whether the data is in
interleaved or parallel (noninterleaved) configuration. Modes 1, 2, 7,
8, and 10 use Tx interleaved data and require either 2× or 4×
interpolation to be enabled.
An optional CLKOUT from IFACE2 is available as a stable
system clock running at the CLKIN frequency or the TxDAC
update rate, which is equal to CLKIN × PLL setting. Setting the
enable IFACE2 register [Register 0x01, Bit 2] enables the
IFACE2 optional clock output. In FD mode, the IFACE2 pin
always acts as a clock output; the enable IFACE2 pin can be
used to invert the IFACE2 output.
•
•
DAC update rate = CLKIN × PLL setting.
Noninterleaved Tx data clock frequency = CLKIN × PLL setting
× 1/(interpolation rate).
Configuration
•
Interleaved Tx data clock frequency = 2 × CLKIN × PLL setting
× 1/(interpolation rate).
The AD9861 timing for the transmit path and for the receive
path depend on the mode setting and various programmable
options. The registers that affect the output clock timing and
data input/output timing are clk_mode [2:0]; enable IFACE2;
inv clkout (IFACE3); Tx inverse sample; interpolation control;
PLL bypass; ADC clock div; Alt timing mode; PLL Div5; PLL
multiplication; and PLL to IFACE2. The clk_mode register is
discussed previously. Table 23 shows the other register bits that
are used to configure the output clock timing and data latching
options available in the AD9861.
The Rx clock does not depend on whether the data is interleaved or
parallel, but does depend on the configuration of the timing mode:
normal or alternative.
•
Normal timing mode, Rx clock frequency = CLKIN × ADC Div
factor (if enabled).
•
Alternative timing mode, Rx clock frequency = CLKIN × PLL
setting × ADC Div factor (if enabled).
Rev. A | Page 46 of 51
Data Sheet
AD9861
Table 23. Serial Registers Related to the Clock Distribution Block
Register Address,
Bit(s)
Register Name
Function
Enable IFACE2
Register 0x01, Bit 2
0: There is no clock output from IFACE2 pin, except in FD mode.
1: The IFACE2 pin outputs a continuous reference clock from the PLL output. In FD mode, this
inverts the IFACE2 output.
Inv clkout (IFACE3)
Tx Inverse Sample
Register 0x01, Bit 1
Register 0x13, Bit 5
0: The IFACE3 clock output is not inverted.
1: The IFACE3 clock output is inverted.
0: The Tx path data is latched relative to the output Tx clock rising edge.
1: The Tx path data is latched relative to the output Tx clock falling edge.
Sets interpolation of 1×, 2×, or 4× for the Tx path.
Interpolation Control
PLL Bypass
Register 0x13, Bit 1:0
Register 0x15, Bit 7
0: The PLL block is used to generate system clock.
1: The PLL block is bypassed to generate system clock.
ADC Clock Div
Alt Timing Mode
PLL Div5
Register 0x15, Bit 5
Register 0x15, Bit 4
Register 0x15, Bit 3
0: ADC clock rate equals the Rx path frequency.
1: ADC clock is one-half the Rx path frequency.
0: CLKIN is used to drive the Rx path clock.
1: PLL block output is used to drive the Rx path clock.
0: PLL block output clock is not divided down.
1: PLL block output clock is divided by 5.
PLL Multiplier
PLL to IFACE2
Register 0x15, Bit 2:0
Register 0x16, Bit 5
Sets multiplication factor of the PLL block to 1× (000), 2× (001), 4× (010), 8× (011), or 16x (100).
0: If enable IFACE2 register is set, IFACE2 outputs buffered CLKIN.
1: If enable IFACE2 register is set, IFACE2 outputs buffered PLL output clock.
Transmit (Tx) timing requires specific setup and hold times to
properly latch data through the data interface bus. These timing
parameters are specified relative to an internally generated output
reference clock. The AD9861 has two interface clocks provided
through the IFACE3 and IFACE2 pins. The transmit timing
specifications, setup and hold time, provide a minimum required
window of valid data.
Table 24. AD9861 Typical Tx Data Latch Timing Relative to
IFACE3 Falling Edge
Mode No.
Mode Name
tsetup (ns)
thold (ns)
1
FD
5
5
5
5
5
5
5
–2.5
2
Optional FD
HD20
–2.5
4
–1.5
5
Optional HD20
HD10
–1.5
Setup time (tSETUP) is the time required for data to initially settle to a
valid logic level prior to the relative output timing edge. Hold time
(tHOLD) is the time after the output timing edge that valid data must
remain on the data bus to be properly latched. Figure 85 shows tSETUP
and tHOLD relative to IFACE3 falling edge. Note that in some cases
negative time is specified, for example with tHOLD timing, which
means that the hold time edge occurs before the relative output clock
edge.
7
–2.5
8
Optional HD10
Clone
–2.5
10
–1.5
Receive (Rx) path data is output after a reference output clock
edge. The time delay of the Rx data relative to a reference
output clock is called the output delay, tOD. The AD9861 has two
possible interface clocks provided through the IFACE3 and
IFACE2 pins. Figure 86 shows tOD relative to IFACE3 rising
edge. Note that in some cases negative time is specified, which
means that the output data transition occurs prior to the relative
output clock edge.
tSETUP
tHOLD
IFACE3 (CLKOUT)
Tx DATA
03606-0-028
tOD
Figure 85. Tx Data Timing Diagram
IFACE3 (CLKOUT)
Rx DATA
Table 24 shows typical setup-and-hold times for the AD9861 in the
various mode configurations.
03606-0-029
Figure 86. Rx Data Timing Diagram
Rev. A | Page 47 of 51
AD9861
Data Sheet
Table 25 shows typical output delay times for the AD9861 in the various mode configurations.
Table 25. AD9861 Rx Data Latch Timing
Mode No.
Mode Name
tOD Data Delay [ns]
+2.5 ns
+1 ns
Relative to:
1
FD
Relative to IFACE2 rising edge
Relative to IFACE3 rising edge
Relative To IFACE3 rising edge
IFACE2 (RxSYNC) relative to LSB
Relative to IFACE3 rising edge
Relative to IFACE3 rising edge
Relative to IFACE3 rising edge
Relative to IFACE3 rising edge
U12 (RxSYNC) relative to LSB
Relative to IFACE3 rising edge
2
Optional FD
+1 ns
+2 ns
4
5
7
8
HD20
−1.5 ns
−0.5 ns
−1.5 ns
+0.5 ns
+0 ns
Optional HD20
HD10
Optional HD10
10
Clone
+1.5 ns
Configuration without Serial Port Interface
(Using Mode Pins)
The AD9861 can be configured using mode pins if a serial port interface is not available. This section applies only to configuring the AD9861
without an SPI. Refer is the Digital Block, Configuring with Mode Pins section for further information.
When using the mode pin option, the pins shown in Table 26 are used to configured the AD9861.
Table 26. Using Mode Pin (SPI Disabled) to Configure Timing (SPI_CS, Pin 64, Must Be Tied Low)
Interpolation
Setting
Interp1,Interp0
Pin 1, Pin 2
HD
Pin 3
20
10/
Pin 17
N/A1
FD/
Clock Mode
PLL Setting
Mode 1 (FD)
2×
4×
1×
2×
4×
2×
4×
2×
4×
Bypassed
2×
4×
2×
4×
1
0, 1
1, 0
0, 0
0, 1
1, 0
0, 1
1, 0
Mode 4 (HD20)
0
0
0
1
Mode 7 (HD10)
1 Pin 17 (IFACE2) is an output clock in FD mode.
Rev. A | Page 48 of 51
Data Sheet
AD9861
OUTLINE DIMENSIONS
DETAIL A
(JEDEC 95)
9.10
9.00 SQ
8.90
0.30
0.25
0.18
PIN 1
INDICATOR
PIN 1
INDIC ATOR AREA OPTIONS
(SEE DETAIL A)
49
64
1
48
0.50
BSC
7.25
7.10 SQ
6.95
EXPOSED
PAD
16
33
32
17
0.50
0.40
0.30
0.25 MIN
BOTTOM VIEW
7.50 REF
TOP VIEW
SIDE VIEW
0.80
0.75
0.70
FOR PROPER CONNECTION OF
THE EXPOSED PAD, REFER TO
THE PIN CONFIGURATION AND
FUNCTION DESCRIPTIONS
0.05 MAX
0.02 NOM
COPLANARITY
0.08
SECTION OF THIS DATA SHEET.
SEATING
PLANE
0.20 REF
COMPLIANT TO JEDEC STANDARDS MO-220-WMMD-4.
Figure 87. 64-Lead Lead Frame Chip Scale Package [LFCSP]
9 mm × 9 mm Body and 0.75 mm Package Height
(CP-64-12)
Dimensions shown in millimeters
ORDERING GUIDE
Model1
Temperature Range
Package Description
64-Lead LFCSP
64-Lead LFCSP
64-Lead LFCSP
64-Lead LFCSP
Package Option
CP-64-12
AD9861BCPZ-50
AD9861BCPZ-80
AD9861BCPZRL-50
AD9861BCPZRL-80
–40°C to +85°C (Ambient)
–40°C to +85°C (Ambient)
–40°C to +85°C (Ambient)
–40°C to +85°C (Ambient)
CP-64-12
CP-64-12
CP-64-12
1 Z = RoHS Compliant Part.
Rev. A | Page 49 of 51
AD9861
NOTES
Data Sheet
Rev. A | Page 50 of 51
Data Sheet
NOTES
AD9861
©2003–2017 Analog Devices, Inc. All rights reserved. Trademarks and
registered trademarks are the property of their respective owners.
D03606-0-4/17(A)
Rev. A | Page 51 of 51
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