OPA4379 [BB]
1.8V, 2.9uA, 90kHz, Rail-to-Rail I/O OPERATIONAL AMPLIFIERS; 1.8V ， 2.9uA ， 90KHz的轨至轨输入/输出运算放大器
| 型号： | OPA4379 |
| 厂家： | 
BURR-BROWN CORPORATION |
| 描述： | 1.8V, 2.9uA, 90kHz, Rail-to-Rail I/O OPERATIONAL AMPLIFIERS |
| 文件： | 总12页 (文件大小：234K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
OPA379
OPA2379
OPA4379
SBOS347A − NOVEMBER 2005 − REVISED DECEMBER 2005
1.8V, 2.9µA, 90kHz, Rail-to-Rail I/O
OPERATIONAL AMPLIFIERS
FD EATURES
DESCRIPTION
LOW NOISE: 2.8µV
PP
The OPA379 family of micropower, low-voltage
D
D
D
microPower: 5.5µA (max)
operational amplifiers is designed for battery-powered
applications. These amplifiers operate on a supply voltage
as low as 1.8V. High-performance, single-supply
operation with rail-to-rail capability makes the OPA379
family useful for a wide range of applications.
LOW OFFSET VOLTAGE: 1.5mV (max)
DC PRECISION:
− CMRR: 100dB
− PSRR: 2µV/V
In addition to microSize packages, the OPA379 family of
op amps features impressive bandwidth (90kHz), low bias
current (25pA), and low noise (80nV/√Hz) relative to the
very low quiescent current (5.5µA max).
− A : 120dB
OL
D
D
WIDE SUPPLY VOLTAGE RANGE: 1.8V to 5.5V
microSize PACKAGES
The OPA379 (single) is available in SC70-5, SOT23-5,
and SO-8 packages. The OPA2379 (dual) comes in
SOT23-8 and SO-8 packages. The OPA4379 (quad) is
offered in a TSSOP-14 package. All versions are specified
from −40°C to +125°C.
AD PPLICATIONS
BATTERY-POWERED INSTRUMENTS
D
D
D
PORTABLE DEVICES
MEDICAL INSTRUMENTS
HANDHELD TEST EQUIPMENT
OPAx379 RELATED PRODUCTS
FEATURES
PRODUCT
OPAx349
TLV240x
TLV224x
TLV27Lx
TLV238x
OPAx347
TLV276x
OPAx348
1µA, 70kHz, 2mV V , 1.8V to 5.5V Supply
OS
1µA, 5.5kHz, 390µV V , 2.5V to 16V Supply
OS
1µA, 5.5kHz, 0.6mV V , 2.5V to 12V Supply
OS
7µA, 160kHz, 0.5mV V , 2.7V to 16V Supply
OS
7µA, 160kHz, 0.5mV V , 2.7V to 16V Supply
OS
20µA, 350kHz, 2mV V , 2.3V to 5.5V Supply
OS
20µA, 500kHz, 550µV V , 1.8V to 3.6V Supply
OS
45µA, 1MHz, 1mV V , 2.1V to 5.5V Supply
OS
Please be aware that an important notice concerning availability, standard warranty, and use in critical applications of Texas Instruments
semiconductor products and disclaimers thereto appears at the end of this data sheet.
All trademarks are the property of their respective owners.
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Copyright 2005, Texas Instruments Incorporated
www.ti.com
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SBOS347A − NOVEMBER 2005 − REVISED DECEMBER 2005
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This integrated circuit can be damaged by ESD. Texas
Instruments recommends that all integrated circuits be
(1)
ABSOLUTE MAXIMUM RATINGS
handledwith appropriate precautions. Failure to observe
proper handling and installation procedures can cause damage.
Supply Voltage . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . +7V
(2)
Signal Input Terminals, Voltage
. . . . . . . . . −0.5V to (V+) + 0.5V
(2)
Current . . . . . . . . . . . . . . . . . . . . 10mA
. . . . . . . . . . . . . . . . . . . . . . . . . . Continuous
ESD damage can range from subtle performance degradation to
complete device failure. Precision integrated circuits may be more
susceptible to damage because very small parametric changes could
cause the device not to meet its published specifications.
(3)
Output Short-Circuit
Operating Temperature . . . . . . . . . . . . . . . . . . . . . −40°C to +125°C
Storage Temperature . . . . . . . . . . . . . . . . . . . . . . . −65°C to +150°C
Junction Temperature . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . +150°C
ESD Rating
ORDERING INFORMATION(1)
PACKAGE
DESIGNATOR
PACKAGE
MARKING
Human Body Model . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 2000V
Charged Device Model . . . . . . . . . . . . . . . . . . . . . . . . . . . 1000V
PRODUCT PACKAGE-LEAD
(2)
OPA379
SC70−5
SOT23−5
SO−8
DCK
DBV
D
AYR
AYQ
(1)
(2)
Stresses above these ratings may cause permanent damage.
OPA379
OPA379
Exposure to absolute maximum conditions for extended periods
may degrade device reliability. These are stress ratings only, and
functional operation of the device at these or any other conditions
beyond those specified is not supported.
OPA379
B61
(2)
OPA2379
OPA2379
SOT23−8
SO−8
DCN
D
OPA2379
OPA4379
(2)
(3)
Input terminals are diode-clamped to the power-supply rails.
Input signals that can swing more than 0.5V beyond the supply
rails should be current-limited to 10mA or less.
(2)
OPA4379
TSSOP−14
PW
(1)
For the most current package and ordering information, see the
Package Option Addendum at the end of this document, or see
the TI web site at www.ti.com.
Short-circuit to ground, one amplifier per package.
(2)
Available Q1, 2006.
PIN CONFIGURATIONS
OPA379
OPA379
OPA379
NC(1)
1
2
3
4
8
7
6
5
NC(1)
V+
V+
+IN
1
2
3
5
4
OUT
1
2
3
5
4
V+
−
V
−
−
V
IN
OUT
−
IN
−
+IN
OUT
NC(1)
+IN
IN
−
V
(3)
SC70−5
(3)
SOT23−5
SO−8
OPA4379
OPA2379
OPA2379
OUT A
1
2
3
4
5
6
7
14 OUT D
1
OUT A
8
V+
OUT A
1
2
3
4
8
7
6
5
V+
−
−
IN D
IN A
13
12 +IN D
−
2
3
4
IN
7
6
5
OUT B
−
IN A
OUT B
+IN A
V+
−
+IN
IN B
−
+IN A
IN B
−
V
11
10 +IN C
−
V
+IN B
−
V
+IN B
+IN B
(2)(3)
SOT23−8
SO−8
−
−
IN B
OUT B
9
8
IN C
OUT C
NOTES:
(1)
(2)
(3)
NC denotes no internal connection.
Pin 1 of the SOT23−8 package is determined by orienting the package marking as shown.
Available Q1, 2006.
(3)
TSSOP−14
2
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SBOS347A − NOVEMBER 2005 − REVISED DECEMBER 2005
ELECTRICAL CHARACTERISTICS: V = +1.8V TO +5.5V
S
Boldface limits apply over the specified temperature range indicated.
At T = +25°C, R = 25kΩ connected to V /2, and V
< (V+) − 1V, unless otherwise noted.
A
L
S
CM
OPA379, OPA2379, OPA4379
PARAMETER
CONDITIONS
MIN
TYP
MAX
UNIT
OFFSET VOLTAGE
Initial Offset Voltage
Over −40°C to +125°C
Drift, −40°C to +85°C
−40°C to +125°C
V
V
S
= 5V
0.4
1.5
mV
mV
OS
2
dV /dT
OS
1.5
2.7
2
µV/°C
µV/°C
µV/V
µV/V
vs Power Supply
PSRR
10
Over −40°C to +125°C
20
INPUT VOLTAGE RANGE
Common-Mode Voltage Range
V
(V−) − 0.1 to (V+) + 0.1
100
V
CM
(1)
Common-Mode Rejection Ratio
Over −40°C to +85°C
CMRR
(V−) < V
(V−) < V
(V−) < V
< (V+) − 1V
< (V+) − 1V
< (V+) − 1V
90
80
62
dB
dB
dB
CM
CM
Over −40°C to +125°C
CM
INPUT BIAS CURRENT
Input Bias Current
I
V
S
= 5V, V < = V /2
CM
5
5
50
50
pA
pA
B
S
Input Offset Current
I
V = 5V
S
OS
INPUT IMPEDANCE
Differential
13
10 || 3
Ω || pF
Ω || pF
13
Common-Mode
10 || 6
NOISE
Input Voltage Noise, f = 0.1Hz to 10Hz
Input Voltage Noise Density, f = 1kHz
Input Current Noise Density, f = 1kHz
2.8
80
1
µV
PP
nV/√Hz
fA/√Hz
e
n
i
n
OPEN-LOOP GAIN
Open-Loop Voltage Gain
Over −40°C to +125°C
A
OL
V
= 5V, R = 25kΩ, 100mV < V < (V+) − 100mV
100
92
120
120
dB
dB
dB
dB
S
L
O
V
S
= 5V, R = 25kΩ, 100mV < V < (V+) − 100mV
L O
V
= 5V, R = 5kΩ, 500mV < V < (V+) − 500mV
100
92
S
L
O
Over −40°C to +125°C
V
= 5V, R = 5kΩ, 500mV < V < (V+) − 500mV
S
L
O
OUTPUT
Voltage Output Swing from Rail
Over −40°C to +125°C
R
= 25kΩ
= 25kΩ
= 5kΩ
5
25
5
10
15
50
75
mV
mV
mV
mV
mA
L
R
L
R
L
Over −40°C to +125°C
Short-Circuit Current
R
= 5kΩ
L
I
SC
Capacitive Load Drive
C
LOAD
See Typical Characteristics Curve
Closed-Loop Output Impedance
Open-Loop Output Impedance
R
G = 1, f = 1kHz, I = 0
O
10
28
Ω
kΩ
OUT
R
O
f = 100kHz, I = 0
O
FREQUENCY RESPONSE
Gain Bandwidth Product
Slew Rate
C
= 30pF
LOAD
GBW
SR
90
0.03
25
kHz
V/µs
µs
G = +1
Overload Recovery Time
Turn-On Time
V
IN
S GAIN > V
S
t
1
ms
ON
POWER SUPPLY
Specified/Operating Voltage Range
Quiescent Current per Amplifier
Over −40°C to +125°C
V
I
1.8
5.5
5.5
10
V
S
V
S
= 5.5V, I = 0
2.9
µA
µA
Q
O
TEMPERATURE
Specified/Operating Range
Storage Range
−40
−65
+125
+150
°C
°C
Thermal Resistance
SC70−5
q
JA
250
200
150
°C/W
°C/W
°C/W
SOT23−5
SOT23−8, TSSOP−14, SO−8
(1)
See Typical Characteristic, Common-Mode Rejection Ratio vs Frequency.
3
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SBOS347A − NOVEMBER 2005 − REVISED DECEMBER 2005
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TYPICAL CHARACTERISTICS
At T = +25°C, V = 5V, R = 25kΩ connected to V /2, unless otherwise noted.
A
S
L
S
COMMON−MODE AND
POWER SUPPLY REJECTION RATIO
vs FREQUENCY
OPEN−LOOP GAIN AND PHASE
vs FREQUENCY
120
100
80
60
40
20
0
120
100
80
60
40
20
0
0
−
−
−
−
−
30
−
PSRR
+PSRR
60
90
120
150
180
CMRR
−
100k
0.1
1
10
100
1k
10k
100k
0.1
1
10
100
1k
10k
Frequency (Hz)
Frequency (Hz)
MAXIMUM OUTPUT VOLTAGE
vs FREQUENCY
QUIESCENT CURRENT
vs SUPPLY VOLTAGE
3.5
3.0
2.5
2.0
1.5
5.0
4.5
4.0
3.5
3.0
2.5
2.0
1.5
1.0
0.5
0
1k
10k
100k
1.5
2.0
2.5
3.0
3.5
4.0
4.5
5.0
5.5
Frequency (Hz)
Supply Voltage (V)
OUTPUT VOLTAGE
vs OUTPUT CURRENT
SHORT−CIRCUIT CURRENT
vs SUPPLY VOLTAGE
2.5
2.0
1.5
1.0
0.5
0
25
20
15
10
5
+ISC
VS
=
2.5V
−
ISC
_
_
_
−
_
+125 C
+85 C
+25 C
40 C
−
0.5
1.0
1.5
2.0
2.5
−
−
−
−
0
1
2
3
4
5
6
7
8
9
10
1.5
2.0
2.5
3.0
3.5
4.0
4.5
5.0
5.5
IOUT (mA)
Supply Voltage (V)
4
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SBOS347A − NOVEMBER 2005 − REVISED DECEMBER 2005
TYPICAL CHARACTERISTICS (continued)
At T = +25°C, V = 5V, R = 25kΩ connected to V /2, unless otherwise noted.
A
S
L
S
OFFSET VOLTAGE vs COMMON−MODE VOLTAGE
vs TEMPERATURE
OFFSET VOLTAGE
PRODUCTION DISTRIBUTION
15000
Unit 1
12500
10000
7500
5000
2500
0
CMRR Specified Range
−
−
−
2500
5000
7500
−
_
40 C
−
−
−
10000
12500
15000
_
+85 C
Unit 2
_
+125 C
0
1
2
3
4
5
Common−Mode Voltage (V)
µ
Offset Voltage ( V)
OFFSET VOLTAGE DRIFT DISTRIBUTION
OFFSET VOLTAGE DRIFT DISTRIBUTION
−
_
_
−
_
_
( 40 C to +85 C)
( 40 C to +125 C)
≤
≤
≤
≤
≤
≤
≤
≤
≤
≤
5
1
2
3
4
5
> 5
1
2
3
4
> 5
µ
_
µ
_
Offset Voltage Drift ( V/ C)
Offset Voltage Drift ( V/ C)
QUIESCENT CURRENT
vs TEMPERATURE
QUIESCENT CURRENT
PRODUCTION DISTRIBUTION
5.0
4.5
4.0
3.5
3.0
2.5
2.0
1.5
1.0
−
−
25
50
0
25
50
75
100
125
_
Temperature ( C)
µ
Quiescent Current ( A)
5
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TYPICAL CHARACTERISTICS (continued)
At T = +25°C, V = 5V, R = 25kΩ connected to V /2, unless otherwise noted.
A
S
L
S
INPUT BIAS CURRENT
vs TEMPERATURE
0.1Hz TO 10Hz NOISE
10000
1000
100
10
1
0.1
0.01
−
−
25
50
0
25
50
75
100
125
2.5s/div
_
Temperature ( C)
SMALL−SIGNAL OVERSHOOT
vs CAPACITIVE LOAD
NOISE vs FREQUENCY
60
50
40
30
20
10
0
1000
100
10
G = +1
−
G =
1
10
100
1000
1
10
100
1k
10k
Capacitive Load (pF)
Frequency (Hz)
SMALL−SIGNAL STEP RESPONSE
LARGE−SIGNAL STEP RESPONSE
µ
25 s/div
µ
50 s/div
6
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SBOS347A − NOVEMBER 2005 − REVISED DECEMBER 2005
APPLICATION INFORMATION
The OPA379 family of operational amplifiers minimizes
power consumption without compromising bandwidth or
+5V
IOVERLOAD
10mA max
noise.
Power-supply
rejection
ratio
(PSRR),
OPA379
VOUT
common-mode rejection ratio (CMRR), and open-loop
VIN
Ω
5k
gain (A ) typical values are 100dB or better.
OL
When designing for ultra-low power, choose system
components carefully. To minimize current consumption,
select large-value resistors. Any resistors will react with
stray capacitance in the circuit and the input capacitance
of the operational amplifier. These parasitic RC
combinations can affect the stability of the overall system.
A feedback capacitor may be required to assure stability
and limit overshoot or gain peaking.
Figure 1. Input Current Protection for Voltages
Exceeding the Supply Voltage
NOISE
Although micropower amplifiers frequently have high
wideband noise, the OPA379 series offer excellent noise
performance. Resistors should be chosen carefully
Good layout practice mandates the use of a 0.1µF bypass
capacitor placed closely across the supply pins.
because the OPA379 has only 2.8µV of 0.1Hz to 10Hz
PP
noise, and 80nV/√Hz of wideband noise; otherwise, they
can become the dominant source of noise.
OPERATING VOLTAGE
OPA379 series op amps are fully specified and tested from
+1.8V to +5.5V. Parameters that vary significantly with
supply voltage are shown in the Typical Characteristics
curves.
CAPACITIVE LOAD AND STABILITY
Follower configurations with load capacitance in excess of
30pF can produce extra overshoot (see typical
characteristic, Small-Signal Overshoot vs Capacitive
Load) and ringing in the output signal. Increasing the gain
enhances the ability of the amplifier to drive greater
capacitive loads. In unity-gain configurations, capacitive
load drive can be improved by inserting a small (10Ω to
INPUT COMMON-MODE VOLTAGE RANGE
The input common-mode voltage range of the OPA379
family typically extends 100mV beyond each supply rail.
This rail-to-rail input is achieved using a complementary
input stage. CMRR is specified from the negative rail to 1V
below the positive rail. Between (V+) − 1V and (V+) + 0.1V,
the amplifier operates with higher offset voltage because
of the transition region of the input stage. See the typical
characteristic, Offset Voltage vs Common-Mode Voltage.
20Ω) resistor, R , in series with the output, as shown in
S
Figure 2. This resistor significantly reduces ringing while
maintaining DC performance for purely capacitive loads.
However, if there is a resistive load in parallel with the
capacitive load, a voltage divider is created, introducing a
Direct Current (DC) error at the output and slightly
reducing the output swing. The error introduced is
proportional to the ratio R /R , and is generally negligible.
S
L
PROTECTING INPUTS FROM
OVER-VOLTAGE
Normally, input currents are 5pA. However, large inputs
(greater than 500mV beyond the supply rails) can cause
excessive current to flow in or out of the input pins.
Therefore, as well as keeping the input voltage below the
maximum rating, it is also important to limit the input
current to less than 10mA. This limiting is easily
accomplished with an input voltage resistor, as shown in
Figure 1.
V+
RS
VOUT
OPA379
Ω
10 to
VIN
CL
RL
Ω
20
Figure 2. Series Resistor in Unity-Gain Buffer
Configuration Improves Capacitive Load Drive
7
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1. Selecting R : Select R such that the current through R
In unity-gain inverter configuration, phase margin can be
reduced by the reaction between the capacitance at the op
amp input and the gain setting resistors, thus degrading
capacitive load drive. Best performance is achieved by
using smaller valued resistors. However, when large
valued resistors cannot be avoided, a small (4pF to 6pF)
capacitor, CFB, can be inserted in the feedback, as shown
in Figure 3. This configuration significantly reduces
F
F
F
is approximately 1000x larger than the maximum bias
current over temperature:
VREF
RF +
ǒ
Ǔ
1000 IBMAX
1.2V
+
(
)
1000 100pA
overshoot by compensating the effect of capacitance, C ,
IN
+ 12MW [ 10MW
(1)
which includes the amplifier input capacitance and PC
board parasitic capacitance.
2. Choose the hysteresis voltage, V . For battery-
HYST
monitoring applications, 50mV is adequate.
3. Calculate R as follows:
1
CFB
RF
VHYST
50mV
ǒ Ǔ + 210kW
ǒ Ǔ+ 10MW
R1 + RF
VBATT
2.4V
(2)
4. Select a threshold voltage for V rising (V
) = 2.0V
THRS
RI
IN
VIN
5. Calculate R as follows:
2
OPA379
VOUT
CIN
1
R2 +
CL
V
THRS
R
1
1
ƪǒ
Ǔ*
ƫ
*
R
F
V
R
REF
1
1
1
+ ƪǒ
Ǔ
2V
1.2V 210kW
1
1
*
*
10MW
Figure 3. Improving Capacitive Load Drive
BATTERY MONITORING
210kW
+ 325kW
(3)
6. Calculate R
: The minimum supply voltage for this
BIAS
circuit will be 1.8V. The REF1112 has a current
requirement of 1.2µA (max). Providing it 2µA of supply
current assures proper operation. Therefore:
The low operating voltage and quiescent current of the
OPA379 series make it an excellent choice for battery
monitoring applications, as shown in Figure 4. In this
circuit, VSTATUS will be high as long as the battery voltage
remains above 2V. A low-power reference is used to set
the trip point. Resistor values are selected as follows:
VBATTMIN
IBIAS
1.8V
2mA
RBIAS
+
+
+ 0.9MW
(4)
RF
R1
+IN
+
IBIAS
OUT
OPA379
VSTATUS
VBATT
−
IN
RBIAS
VREF
R2
REF1112
Figure 4. Battery Monitor
8
ꢂ ꢀꢉ ꢠꢡꢢ
ꢂ ꢀꢉ ꢣꢠꢡ ꢢ
ꢂ ꢀꢉ ꢤꢠꢡ ꢢ
www.ti.com
SBOS347A − NOVEMBER 2005 − REVISED DECEMBER 2005
LOW-SIDE CURRENT MONITOR
WINDOW COMPARATOR
The micropower OPA379 is well suited for current
monitoring circuits in applications such as a voltage
regulator with fold-back current limiting, or a high-current
power supply with crowbar protection. Figure 5 shows the
OPA379 monitoring the current in a power-supply return
path using a 0.1Ω shunt resistor. The NPN transistor, Q1
(2N2222 or equivalent) is used to generate equal voltages
at the inverting and noninverting inputs. Therefore, the
Figure 6 shows the OPA2379 used as a window
comparator. The threshold limits are set by V and V , with
H
L
V > V . When V < V , the output of A1 will be low. When
H
L
IN
H
V
>V , the output of A2 will be low. Therefore, both op
IN
L
amp outputs will be at 0V as long as V is between V and
IN
H
V . This results in no current flowing through either diode,
L
Q1 in cutoff, with the base voltage at 0V, and V
high.
forced
OUT
voltage drops across R and R are equal, and the current
1
S
If V falls below V , the output of A2 will be high, current
IN
L
flowing through Q1 is directly proportional to the current
flowing through R . As the load current increases, the
will flow through D2, and V
will be low. Likewise, if V
OUT
IN
S
rises above V , the output of A1 will be high, current will
H
current through Q1 increases, the voltage drop across R
2
flow through D1, and V
will be low.
OUT
increases, and this decreases the output voltage, V
shown in Equation (5):
, as
OUT
The window comparator threshold voltages are set as
follows:
R2
R1
+ GND * ǒ
Ǔ
VOUT
RS IL
R2
R1 ) R2
VH +
(6)
(7)
2.49kW
100W
+ 0V * ǒ
Ǔ
0.1W IL
R4
R3 ) R4
VL +
+ * 2.49W IL
(5)
3V
3V
R1
R2
5V
VH
A1
D1(2)
1/2
3V
R2
2.49k
OPA2379
Ω
Ω
5.1k
VOUT
VOUT
RIN
(1)
Ω
2k
Ω
10k
Q1(3)
Q1
VIN
5V
Ω
5.1k
3V
3V
A2
OPA379
D2(2)
R1
100
1/2
R3
OPA2379
Ω
VL
RS
Ω
0.1
R4
Return to Ground
IL
NOTES: (1) RIN protects A1 and A2 from possible excess current flow.
(2) IN4446 or equivalent diodes.
(3) 2N2222 or equivalent NPN transistor.
Figure 5. Low-Side Current Monitor
Figure 6. OPA2379 as a Window Comparator
9
PACKAGE OPTION ADDENDUM
www.ti.com
4-Mar-2006
PACKAGING INFORMATION
Orderable Device
OPA2379AID
Status (1)
ACTIVE
ACTIVE
ACTIVE
ACTIVE
ACTIVE
ACTIVE
ACTIVE
ACTIVE
Package Package
Pins Package Eco Plan (2) Lead/Ball Finish MSL Peak Temp (3)
Qty
Type
Drawing
SOIC
D
8
8
8
8
8
8
8
8
75 Green (RoHS & CU NIPDAU Level-2-260C-1 YEAR
no Sb/Br)
OPA2379AIDG4
OPA2379AIDR
OPA2379AIDRG4
OPA379AID
SOIC
SOIC
SOIC
SOIC
SOIC
SOIC
SOIC
D
D
D
D
D
D
D
75 Green (RoHS & CU NIPDAU Level-2-260C-1 YEAR
no Sb/Br)
2500 Green (RoHS & CU NIPDAU Level-2-260C-1 YEAR
no Sb/Br)
2500 Green (RoHS & CU NIPDAU Level-2-260C-1 YEAR
no Sb/Br)
75 Green (RoHS & CU NIPDAU Level-2-260C-1 YEAR
no Sb/Br)
OPA379AIDG4
OPA379AIDR
75 Green (RoHS & CU NIPDAU Level-2-260C-1 YEAR
no Sb/Br)
2500 Green (RoHS & CU NIPDAU Level-2-260C-1 YEAR
no Sb/Br)
OPA379AIDRG4
2500 Green (RoHS & CU NIPDAU Level-2-260C-1 YEAR
no Sb/Br)
(1) The marketing status values are defined as follows:
ACTIVE: Product device recommended for new designs.
LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect.
NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in
a new design.
PREVIEW: Device has been announced but is not in production. Samples may or may not be available.
OBSOLETE: TI has discontinued the production of the device.
(2)
Eco Plan - The planned eco-friendly classification: Pb-Free (RoHS), Pb-Free (RoHS Exempt), or Green (RoHS & no Sb/Br) - please check
http://www.ti.com/productcontent for the latest availability information and additional product content details.
TBD: The Pb-Free/Green conversion plan has not been defined.
Pb-Free (RoHS): TI's terms "Lead-Free" or "Pb-Free" mean semiconductor products that are compatible with the current RoHS requirements
for all 6 substances, including the requirement that lead not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered
at high temperatures, TI Pb-Free products are suitable for use in specified lead-free processes.
Pb-Free (RoHS Exempt): This component has a RoHS exemption for either 1) lead-based flip-chip solder bumps used between the die and
package, or 2) lead-based die adhesive used between the die and leadframe. The component is otherwise considered Pb-Free (RoHS
compatible) as defined above.
Green (RoHS & no Sb/Br): TI defines "Green" to mean Pb-Free (RoHS compatible), and free of Bromine (Br) and Antimony (Sb) based flame
retardants (Br or Sb do not exceed 0.1% by weight in homogeneous material)
(3)
MSL, Peak Temp. -- The Moisture Sensitivity Level rating according to the JEDEC industry standard classifications, and peak solder
temperature.
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Addendum-Page 1
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