L84225 [ETC]
L84225 100BaseTX/FX/10BaseT Physical Layer Device technical manual 4/02 ; L84225 100BaseTX的/ FX /的10BaseT物理层设备技术手册4/02型号: | L84225 |
厂家: | ETC |
描述: | L84225 100BaseTX/FX/10BaseT Physical Layer Device technical manual 4/02
|
文件: | 总118页 (文件大小:829K) |
中文: | 中文翻译 | 下载: | 下载PDF数据表文档文件 |
®
L84225100BaseTX/FX/10BaseT
Physical Layer Device
Technical Manual
Features
•
Single-chip 100BaseTX/100BaseFX/
10BaseT physical layer solution
•
•
Meets all applicable IEEE 802.3,
10BaseT, 100BaseTX and 100BaseFX
standards
•
•
•
•
•
Four independent Channels in One IC
3.3 V power supply with 5 V tolerant I/O
Dual Speed - 10/100 Mbps
On-chip wave shaping - no external
filters required
•
•
•
Adaptive Equalizer for 100BaseTX
Baseline Wander Correction
LED outputs
Half and Full Duplex
MII interface or reduced pin count MII
(RMII) interface to Ethernet Controller
–
–
–
–
Link, Activity, Collision
Full Duplex
•
•
•
MI interface for configuration and status
Optional Repeater Interface
Far End Fault (for FX)
10/100
AutoNegotiation for 10/100, Full/Half
Duplex hardware controlled
advertisement
•
160L PQFP
Contents
Description - - - - - - - - - - - - - - - - - - - - - 2 Specifications - - - - - - - - - - - - - - - - - - - 87
Pin Description - - - - - - - - - - - - - - - - - - 4 Ordering Information - - - - - - - - - - - - - 114
Functional Description - - - - - - - - - - - - -13 Revision History - - - - - - - - - - - - - - - - 114
Register Description- - - - - - - - - - - - - - -57 Surface Mount Packages- - - - - - - - - - 117
Application Information- - - - - - - - - - - - -70
Note:
Check for the latest revision of this document before start-
ing any designs. This document is available on the Web, at
www.lsilogic.com
MD400183/B
April, 2002
1 of 118
Copyright © 1999-2002 by LSI Logic Corporation. All rights reserved.
Description
The L84225 is a highly integrated Ethernet Transceiver for twisted pair
and fiber Ethernet applications. The L84225 can be configured for either
100 Mbps (100BaseFX or 100BaseTX) or 10 Mbps (10BaseT) Ethernet
operation.
The L84225 consists of four (4) separate and independent channels.
Each channel consists of: 4B5B/Manchester encoder, scrambler,
transmitter with wave shaping and on-chip filters, transmit output driver,
receiver with adaptive equalizer, filters, baseline wander correction, clock
and data recovery, descrambler, 4B5B/Manchester decoder, and
controller interface (MII or RMII).
The addition of internal output waveshaping circuitry and on-chip filters
eliminates the need for external filters normally required in 100BaseTX
and 10BaseT applications.
The L84225 can automatically configure itself for 100 or 10 Mbps and
Full or Half Duplex operation, for each channel independently, using the
on-chip AutoNegotiation algorithm.
The L84225 can access eleven 16-bit registers for each channel through
the Management Interface (MI) serial port. These registers comply with
Clause 22 of IEEE 802.3u and contain configuration inputs, status
outputs, and device capabilities.
The L84225 is ideal as a media interface for 100BaseTX/
100BaseFX/10BaseT switching hubs, repeaters, routers, bridges, and
other multi port applications.
The L84225 is implemented in a low power CMOS technology and
operates with a 3.3V power supply.
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L84225 Quad 100BaseTX/FX/10BaseT Phys. Layer Device - Technical Manual
Copyright © 1999-2002 by LSI Logic Corporation. All rights reserved.
Pin Configuration
LED0_3
LED1_3
LED2_3
LED0_2
LED1_2
LED2_2
GND
LED0_1
LED1_1
LED2_1
LED0_0
LED1_0
LED2_0
GND
1
2
3
4
5
6
7
8
120
119
118
117
116
115
114
113
112
111
110
109
108
107
106
105
104
103
102
101
100
99
98
97
96
95
94
93
92
91
90
89
88
87
86
85
84
83
SPEED_3
SPEED_2
CLKIN
LED3_3
LED3_2
LED3_1
LED3_0
SPEED_1
SPEED_0
ANEG
9
10
11
12
13
14
15
16
17
18
19
20
21
22
23
24
25
26
27
28
29
30
31
32
33
34
35
36
37
38
39
40
LEDDEF
RESET
GND
VDD
VDD
VDD
DPLX_0
DPLX_1
DPLX_2
DPLX_3
REPEATER
RMII_EN
VDD
MDC
REGDEF
MDIO
AD_REV
PHYAD2
PHYAD3
PHYAD4
GND
L84225
160 PQFP
Top View
VDD
RXD3_0
RXD2_0
RXD1_0
RXD0_0
RXDV_0
RXCLK_0
RXER_0/RXD4_0
TXER_0/TXD4_0
TXCLK_0
TXEN_0
TXD0_0
TXD1_0
TXD2_0
TXD3_0
COL_0
VDD
GND
CRS_3
COL_3
TXD3_3
TXD2_3
TXD1_3
TXD0_3
TXEN_3
TXCLK_3
TXER_3/TXD4_3
RXER_3/RXD4_3
RXCLK_3
RXDV_3
RXD0_3
RXD1_3
CRS_0
GND
VDD
82
81
Description
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April, 2002
Copyright © 1999-2002 by LSI Logic Corporation. All rights reserved.
1 Pin Description
Pin Description
Power Supplies
Pin #
Pin Name
I/O
Description
Positive Supply. +3.3 5%Volts.
15
16
VDD
---
22
40
41
60
78
96
100
107
125
128
132
135
144
147
151
154
7
GND
---
Ground. 0 Volts.
14
21
39
56
59
77
95
108
121
122
127
131
134
141
146
150
153
160
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L84225 Quad 100BaseTX/FX/10BaseT Phys. Layer Device - Technical Manual
Copyright © 1999-2002 by LSI Logic Corporation. All rights reserved.
Pin Description (Cont.)
Media Interface
Pin # Pin Name
I/O
Description
126
136
145
155
TPOP_[3:0]/
FXIN_[3:0]
I/O
Twisted Pair Transmit Output, Positive.
Fiber Receive Input, Negative.
129
133
148
152
TPON_[3:0]/
FXIP_[3:0]
I/O
I/O
I/O
I
Twisted Pair Transmit Output, Negative.
Fiber Receive Input, Positive.
123
139
142
158
TPIP_[3:0]/
FXOP_[3:0]
Twisted Pair Receive Input, Positive.
Fiber Transmit Output, Positive.
124
138
143
157
TPIN_[3:0]/
FXON_[3:0]
Twisted Pair Receive Input, Negative.
Fiber Transmit Output, Negative.
130
137
149
156
SD_[3:0]/
FXEN_[3:0]
Fiber Interface Signal Detect Input.
Fiber Interface Enable.
When this pin in not tied to GND, the fiber interface is enabled and
this pin becomes a Signal Detect ECL input. The trip point for this
ECL input is determined by the voltage applied to the SD_THR
pin. When this pin is tied to GND, the fiber interface is disabled
(i.e., TP Interface is enabled).
159
140
SD_THR
REXT
---
---
Fiber Interface Signal Detect Threshold Reference.
The voltage applied to this pin sets the reference level for the fiber
interface SD input pin so that the device can directly connect SD
pin to both 3.3V and 5V fiber optic transceivers. Typically, this pin
is either tied to GND (for 3.3V) or to an external voltage divider (for
5V).
Transmit Current Set.
An external resistor connected between this pin and GND will set
the level for the transmit outputs.
Pin Description
Copyright © 1999-2002 by LSI Logic Corporation. All rights reserved.
5 of 118
April, 2002
Pin Description (Cont.)
Controller Interface (MII & RMII)
Pin # Pin Name
I/O
Description
87
69
50
31
TXCLK_[3:0]
TXEN_[3:0]
O
Transmit Clock Output. These interface outputs provide clocks to
external controllers. Transmit data from the controller on TXD,
TXEN, and TXER is clocked in on the rising edges of TXCLK and
CLKIN.
88
70
51
32
I
I
I
Transmit Enable Input. These interface inputs must be asserted
active high to allow data on TXD and TXER to be clocked in on
the rising edges of TXCLK and CLKIN.
[92:89] TXD[3:0]_3
[74:71] TXD[3:0]_2
[55:52] TXD[3:0]_1
[36:33] TXD[3:0]_0
Transmit Data Input. These interface inputs contain input nibble
data to be transmitted on the TP or FX outputs and are clocked in
on rising edges of TXCLK and CLKIN. In RMII mode, only
TXD[1:0] are used.
86
68
49
30
TXER_[3:0]/
TXD4_[3:0]
Transmit Error Input. These interface inputs initiate an error pat-
tern to be transmitted on the TP or FX outputs and are clocked in
on rising edges of TXCLK when TXEN is asserted.
If the channel is placed in the Bypass 4B5B Encoder mode, these
pins are reconfigured to be the fifth TXD transmit data input,
TXD4. In RMII mode, these pins are not used.
84
66
47
28
RXCLK_[3:0]
CRS_[3:0]
O
O
O
O
Receive Clock Output. These interface outputs provide a clock to
the controller. Receive data on RXD, RXDV, and RXER is clocked
out to the controller on falling edges of RXCLK.
94
76
58
38
Carrier Sense Output. These interface outputs are asserted
active high when valid data is detected on the receive TP or FX
inputs and is clocked out on the falling edge of RXCLK.
83
65
46
27
RXDV_[3:0]
Receive Data Valid Output. These interface outputs are asserted
active high when valid decoded data is present on the RXD out-
puts and is clocked out on falling edges of RXCLK. In RMII mode,
these pins are not used.
[79:82] RXD[3:0]_3
[61:64] RXD[3:0]_2
[42:45] RXD[3:0]_1
[23:26] RXD[3:0]_0
Receive Data Output. These interface outputs contain recovered
nibble data from the TP or FX inputs and are clocked out on the
falling edges of RXCLK. In RMII mode, only RXD[1:0] are used.
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Pin Description (Cont.)
Controller Interface (MII & RMII) [Continued]
Pin # Pin Name
I/O
Description
85
67
48
29
RXER_[3:0]/
RXD4_[3:0]
O
Receive Error Output. These interface outputs are asserted
active high when coding or other specified errors are detected on
the TP or FX inputs and are clocked out on falling edges of
RXCLK.
If the channel is placed in the Bypass 4B5B Decoder mode, these
pins are reconfigured to be the fifth RXD receive data output,
RXD4.
93
75
57
37
COL_[3:0]
O
Collision Output. These interface outputs are asserted active
high when collision between transmit and receive data is detected.
Management Interface (MI)
Pin # Pin Name I/O
Description
99
97
MDC
I
Management Interface (MI) Clock Input. This MI clock shifts
serial data into and out of MDIO on rising edges.
MDIO
I/O
Management Interface (MI) Data Input/Output. This bidirectional
pin contains serial data that is clocked in and out on rising edges
of the MDC clock.
98
REGDEF
I
Invalid Register Read Select This active low input controls the
Pullup default values that are read from invalid (unused) register
locations.
1 = All unused register locations return a value of ‘0000’ when
read.
0 = All unused register locations return a value of ‘ffff’ when read.
Note: Not available on Rev. B product. On Rev. B product all
invalid register locations return a value of ‘0000’ when read.
20
19
18
PHYAD[4:2]
I
MI Physical Device Address Input. These pins set the three
most significant bits of the PHY address. The two least significant
bits of the PHY address are set internally to match the channel
number, as shown below:
PHYAD1
PHYAD0
Channel 3
Channel 2
Channel 1
Channel 0
1
1
0
0
1
0
1
0
Pin Description
Copyright © 1999-2002 by LSI Logic Corporation. All rights reserved.
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April, 2002
Pin Description (Cont.)
LED Drivers
Pin # Pin Name
I/O
Description
117
116
115
114
LED3_[3:0]
LED2_[3:0]
LED1_[3:0]
LED0_[3:0]
LEDDEF
O
LED Output. The default functions of these pins are 100 Mbps
Link Detect outputs assuming LEDDEF = 0. These pins can drive
an LED from both VDD and GND.
Please refer to Table 2 for LED description
3
6
10
13
O
O
O
I
LED Output. The default functions of these pins are Activity
Detect outputs assuming LEDDEF = 0. These pins can drive an
LED from both VDD and GND.
Please refer to Table 2 for LED description
2
5
9
LED Output. The default functions of these pins are Full Duplex
Detect outputs assuming LEDDEF = 0. These pins can drive an
LED from both VDD and GND.
12
Please refer to Table 2 for LED description
1
4
8
LED Output. The default functions of these pins are 10 Mbps Link
Detect outputs assuming LEDDEF = 0. These pins can drive an
LED from both VDD and GND.
11
Please refer to Table 2 for LED description.
110
LED Default Select Input. This pin changes the default selection
for the LEDs in the MI Serial Port Global Configuration Register.
1 = LINK + ACT, COL, FDX, 10/100
0 = LINK100, ACT, FDX, LNK10
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Pin Description (Cont.)
Miscellaneous
Pin # Pin Name
I/O
Description
111
ANEG
I
AutoNegotiation Enable Input. This digital input, ANDed with
register bit 0.12, enables AutoNegotiation for all channels.
1 = AutoNegotiation On & Combined with Speed and Duplex pins,
control advertisement. See Table 1 for the different combinations.
0 = Off
120
119
113
112
SPEED_[3:0]
DPLX_[3:0]
I
I
Speed Selection Input. These digital inputs, ANDed with register
bit 0.13, select speed in each corresponding channel. Please refer
to Table 1 for the different combinations.
1 = 100 Mbps Mode
0 = 10 Mbps Mode
103
104
105
106
Duplex Selection Input. These digital inputs, ORed with register
bit 0.8, select the duplex mode in EACH corresponding channel.
They control advertisement when ANEG is enabled. See Table 1
for the different combinations.
1 = Full Duplex Mode
0 = Half Duplex Mode
102
REPEATER
I
Repeater Mode Enable Input. This digital input, ORed with reg-
ister bit 17.14, enables repeater mode for ALL channels.
1 = Repeater Mode Enabled
0 = Normal Operation
101
17
RMII_EN
AD_REV
I
I
Reduced Pin Count MII Interface Enable.
1 = RMII Mode Enabled
0 = MII Enabled
Address Reverse Input.
Pullup 1 = Normal
In this mode, physical ports 0-3 are mapped to MI addresses 0-3
in the same order.
0 = Reverse Address Mode Select
In this mode, physical ports 0-3 are mapped to MI addresses 3-0
respectively. This is the reverse to the normal order.
118
109
CLKIN
I
I
Clock Input. In MII mode, there must be a 25 MHz clock input to
this pin. In RMII mode, there must be a 50 MHz clock input to this
pin. TXCLK is generated from the input to this pin.
RESET
Hardware Reset Input.
Pullup 1 = Normal
0 = Device In Reset State
(Reset is complete 50 ms after RESET goes high).
Pin Description
Copyright © 1999-2002 by LSI Logic Corporation. All rights reserved.
9 of 118
April, 2002
Table 1
AutoNegotiation, Speed & Duplex Mode Combinations
Input Pins
Mode Selected
Forced Modes [Note2] Advertised Capabilities
Speed
[3:0]
Duplx
[3:0]
Aneg
Autoneg
Speed
DPLX
Speed
DPLX
0
0
0
0
1
1
1
1
0000
0000
1111
1111
0000
0000
1111
1111
0000
1111
0000
1111
0000
1111
0000
1111
Off
Off
Off
Off
On
On
On
On
10
10
Half
Full
Half
Full
na
na
na
na
na
100
100
na
na
na
na
na
10
Half
na
na
10
Half/Full
Half/Full [3]
Half
na
na
10/100
10/100
na
na
Note 1: The single ANEG pin applies to all four channels. The four
Speed and DPLX apply to each individual channel. The pins above are
shown for all four channels, but each channel can be individually
configured for SPEED and DPLX by appropriately setting the pin for that
channel.
Note 2: Forced Modes assume that registers 0 and 4 are at default
values.
Note 3: the L84225 can be controlled either through the software or
through the hardware. If the device needs to be controlled through the
software (Registers 0 to 4), then these seven pins (ANEG, Speed[3:0],
Duplx[3:0]) have to be tied to their default values of 1, 1111, and 0000,
respectively.
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L84225 Quad 100BaseTX/FX/10BaseT Phys. Layer Device - Technical Manual
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Table 2
Name
LED Definitions as per the LEDDEF Pin
Output State Description
LEDtied LEDtied
to GND
to Vdd LEDDEF
LED01
0 = 100 Mbps Link Detected
1 = 10 Mbps Link Detected
3-state = No Link
Off
On
Off
Off
On
Off
Off
On
Off
Blink
On
Off
On
Off
On
Off
Off
On
Off
Off
On
Off
Off
On
Off
On
Blink
Off
On
Off
On
Off
Off
On
LEDDEF = 1
(10/100)
LED1
0 = Full Duplex Mode Detect with Link Pass
1 = Half Duplex Mode Detect with Link Pass
3-state = No Link
(Fdx/Hdx)
LED2
(Col)
0 = Collision Detect
1 = No Collision
LED3
0 = Link Detect
(Link + Act) Blink = Link Detect + Activity
1 = No Link Detect or Activity
LED01
0 = 10 Mbps Link Detected
LEDDEF = 0
(Link10)
LED1
1 = No 10 Mbps Link Detected
0 = Full Duplex Mode Detect with Link Pass
1 = Half Duplex Mode Detect with Link Pass
3-state = No Link
(Fdx/Hdx)
LED2
Blink = Activity Occurred
(Stretch pulse to 100 ms)
(Act)
1 = No Activity
0 = Link100 Detected
1 = No Link100
Detected
On
Off
On
Off
On
Off
LED3
(Link100)
1. LED 0 becomes FEF when FX Interface is enabled.
0 = FEF detected
1 = No FEF detected
Pin Description
Copyright © 1999-2002 by LSI Logic Corporation. All rights reserved.
11 of 118
April, 2002
Figure 1
L84225 Block Diagram
Global
Global
Per Channel Functions
100BaseFX Transmitter
NRZI
Encoder
ANEG
SPEED_[3:0]
DPLX_[3:0]
+
−
100BaseTX Transmitter
AD_REV
REPEATER
TPOP_3
4B5B
Encoder
MLT3
Encoder
Current
Source
LP
Filter
+
−
Scrambler
RESET
CLKIN
TPON_3
Clock
Generator
MDC
MDIO
PHYAD[4:2]
Serial
Port
(MI)
REXT
10BaseT Transmitter
ROM
REGDEF
LP
Filter
Manchester
Encoder
+
−
DAC
Clock
Generator
TXCLK_3
TXD[3:0]_3
TXEN_3
SD_THR
100BaseFX Receiver
TXER_3/TXD4_3
COL_3
Controller
Interface
+
−
SD/FXEN_3
Collision
Vth
±Vth
RXCLK_3
RXD[3:0]_3
CRS_3
+
NRZI
Decoder
+
−
RXDV_3
RXER_3/RXD4_3
100BaseTX Receiver
Squelch
Clock
& Data
Recovery
4B5B
Decoder
Descrambler
LEDDEF
+
−
TPIP_3
MLT3
Decoder
Adaptive
Equalizer
LED3_3
LED2_3
LED1_3
LED0_3
TPIN_3
LED
Drivers
Auto-
Negotiation
& Link
10BaseTX Receiver
Squelch
± Vth
Clock & Data
Recovery
(Manchester
Decoder)
+
+
−
LP
Filter
Channel 3
Channel 2
Channel 1
Channel 0
2 Functional Description
2.1 General
The L84225 is a complete 10/100 Mbps Ethernet Media Interface IC. The
L84225 has four separate and independent channels. Each channel has
the following main sections: controller interface, encoder, decoder,
scrambler, descrambler, clock and data recovery, twisted pair and fiber
interface transmitter, twisted pair and fiber interface receiver, and auto
negotiation. A Management Interface (MI) serial port, which provides
access to eleven registers for each channel, is common to all four
channels. Figure 1 shows the L84225 block diagram.
The L84225 can operate as a 100BaseTX or 100BaseFX device (100
Mbps mode) or as a 10BaseT device (10 Mbps mode). The 100 Mbps
and 10 Mbps modes differ in data rate, signaling protocol, and allowed
wiring as follows:
•
•
•
The 100 Mbps FX mode uses two fiber connections with 4B5B
encoded NRZI 125 MHz binary data through an ECL-type driver to
achieve a throughput of 100 Mbps.
The 100 Mbps TX mode uses two pairs of category 5, or better, UTP
or STP twisted pair cable with 4B5B encoded, scrambled, and MLT3
coded (ternary) 125 MHz data to achieve a throughput of 100 Mbps.
The 10 Mbps mode uses two pairs of category 3, or better, UTP or
STP twisted pair cable with Manchester encoded 10 MHz binary data
to achieve a 10 Mbps thruput.
The data symbol format on the fiber or twisted pair cable for the 100 and
10 Mbps modes is defined in IEEE 802.3 specifications and shown in
Figure 2.
Functional Description
Copyright © 1999-2002 by LSI Logic Corporation. All rights reserved.
13 of 118
April, 2002
Figure 2
Frame Format
Ethernet MAC Frame
SFD DA SA
Interframe
GAP
Interframe
GAP
LLC Data
PREAMBLE
LN
LN
FCS
100 Base-TX Data Symbols
IDLE
IDLE
IDLE
SSD PREAMBLE
SFD
DA
SA
LLC DATA FCS ESD IDLE
[ 1 1 1 1 ...]
[ 1 1 0 0 0 1 0 0 0 1 ]
[ 1 0 1 0 ...] 62 Bits Long
[ 1 1 ]
[ DATA ]
IDLE =
SSD =
Before/After
4B5B Encoding,
Scrambling, and
MLT3 Coding
PREAMBLE =
SFD =
DA, SA, LN, LLC DATA, FCS =
ESD =
[ 0 1 1 0 1 0 0 1 1 1 ]
100 Base-FX Data Symbols
SSD PREAMBLE
SFD
DA
SA
LN
LLC DATA FCS ESD IDLE
[ 1 1 1 1 ...]
[ 1 1 0 0 0 1 0 0 0 1 ]
[ 1 0 1 0 ...] 62 Bits Long
[ 1 1 ]
[ DATA ]
IDLE =
SSD =
Before/After
4B5B Encoding
PREAMBLE =
SFD =
DA, SA, LN, LLC DATA, FCS =
ESD =
[ 0 1 1 0 1 0 0 1 1 1 ]
10 Base-T Data Symbols
SFD DA SA
PREAMBLE
LN
LLC DATA FCS SOI
IDLE
[ NoTransitions ]
IDLE =
[ 1 0 1 0 ...] 62 Bits Long
[ 1 1 ]
PREAMBLE =
SFD =
DA, SA, LN, LLC DATA, FCS =
Before/After
Manchester
Encoding
[ DATA ]
[ 1 1 ] With No MID Bit
Transition
SOI =
On the transmit side for 100 Mbps operation, data is received on the
controller interface from an external Ethernet controller per the format
shown in Figure 3. The data is sent to the encoder for formatting. For TX
operation, the encoded data is sent to the scrambler. The encoded and
scrambled data is then sent to the TX transmitter. The transmitter
converts the encoded and scrambled data into MLT3 ternary format. The
transmitter then pre-shapes the output and drives the twisted pair cable.
14 of 118
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L84225 Quad 100BaseTX/FX/10BaseT Phys. Layer Device - Technical Manual
Copyright © 1999-2002 by LSI Logic Corporation. All rights reserved.
For FX operation, the encoded data is converted to NRZI format, which
drives a binary (two-level) signal to the fiber transceiver interface (PMD).
On the receive side for 100BaseTX operation, the TX receiver removes
any high frequency noise from the input, equalizes the input signal to
compensate for the low pass effects of the cable, and qualifies the data
with a squelch algorithm. The TX receiver then converts the data from
MLT3 coded twisted pair levels to internal digital levels. The output of the
receiver then goes to a clock and data recovery block which recovers a
clock from the incoming data, uses the clock to latch in valid data into
the device, and converts the data back to NRZ data. The data is then
unscrambled and decoded by the 4B5B decoder and descrambler,
respectively, and output to an external Ethernet controller by the
controller interface. 100Base FX receiver operation is the same as TX
except there is no equalizer, descrambler, and has a separate ECL
receiver.
10 Mbps operation is similar to the 100 Mbps operation, except:
•
•
•
•
There is no scrambler/descrambler.
The encoder/decoder is Manchester instead of 4B5B.
The data rate is 10 Mbps instead of 100 Mbps.
The twisted pair symbol data is two level Manchester instead of
ternary MLT3.
The FX interface is disabled for 10 Mbps operation.
The AutoNegotiation block automatically configures each channel for
either 100BaseTX or 10BaseT, and either Full or Half Duplex operation.
This configuration is based on the capabilities selected for the channel
and capabilities detected from the remote device connected to the
channel.
The Management Interface (the MI serial port) is a two-pin bidirectional
link through which configuration inputs can be set and channel status
outputs read.
Each block plus the operating modes are described in more detail in the
following sections. Since the L84225 can operate as a 100BaseFX,
100BaseTX, or 10BaseT device, each of the following sections describes
the performance in both 100 and 10 Mbps modes.
Functional Description
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2.2 Controller Interface
2.2.1 General
The L84225 has three interfaces to an external controller: Media
Independent Interface (MII), Reduced pin MII (RMII), and Five Bit
Interface (FBI). MII is the default interface. RMII is selected by asserting
the RMII_EN pin, a global control (all channels effected). FBI is selected,
on a per port basis, by setting the bypass encoder bit in the MI serial
port Channel Configuration register (Register 17).
2.2.2 MII - 100 Mbps
The MII is a nibble-wide packet data interface defined in IEEE 802.3. The
L84225 meets all MII requirements outlined in IEEE 802.3. The L84225
can directly connect, without external logic, to any Ethernet controller or
other device that also complies with the IEEE 802.3 MII specification.
The MII frame format is shown in Figure 3.
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Figure 3
MII Frame Format
a. MII Frame Format
TXEN = 1
TX_EN = 0
IDLE
TXEN = 0
IDLE
Start of
Frame
PREAMBLE
PRMBLE
DATA Nibbles
SFD
DATA 1 DATA 2 DATA N-1 DATA N
62 Bits
2 Bits
PREAMBLE = [ 1 0 1 0 ...] 62 Bits Long
SFD = [ 1 1 ]
DATAn = [Between 64−1518 Data Bytes]
IDLE = TXEN = 0
b. MII Nibble Order
First Bit
LSB
First
Nibble
MACs Serial Bit Stream
D0
D1
D2
D3
D4
D5
D6
D7
MSB
Second
Nibble
TXD0/RXD0
TXD1/RXD1
TXD2/RXD2
TXD3/RXD3
MII
Nibble
Stream
c. Transmit Preamble and SFD Bits
Signals
Bit Value
1
2
3
3
TXD0
TXD1
TXD2
TXD3
TXEN
X
X
X
X
0
X
X
X
X
0
1
1
0
1
0
1
1
0
1
0
1
1
0
1
0
1
1
0
1
0
1
1
0
1
0
1
1
0
1
0
1
1
0
1
0
1
1
0
1
0
1
1
0
1
0
1
1
0
1
0
1
1
0
1
0
1
1
0
1
0
1
1
0
1
0
1
1
1
D0 D4
D1 D5
D2 D6
D3 D7
0
0
0
1
1
1
1
0
1
1
0
1
1
1
1. 1st preamble nibble transmitted.
2. 1st SFD nibble transmitted.
3. 1st data nibble transmitted.
4. D0 thru D7 are the first 8 bits of the data field.
d. Receive Preamble and SFD Bits
Signals
Bit Value
1
2
3
3
RXD0
RXD1
RXD2
RXD3
RXDV
X
X
X
X
0
X
X
X
X
0
1
1
0
1
0
1
1
0
1
0
1
1
0
1
0
1
1
0
1
0
1
1
0
1
0
1
1
0
1
0
1
1
0
1
0
1
1
0
1
0
1
1
0
1
0
1
1
0
1
0
1
1
0
1
0
1
1
0
1
0
1
1
0
1
0
1
1
1
0
1
1
1
D0 D4
D1 D5
D2 D6
D3 D7
0
0
1
0
1
1
0
1
1
1
1. 1st preamble nibble received. Depending on mode, device may eliminate either all or some of the preamble
nibbles, up to 1st SFD nibble.
2. 1st SFD nibble received.
3. 1st data nibble received.
4. D0 thru D7 are the first 8 bits of the data field.
Functional Description
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The MII consists of four transmit data bits (TXD[3:0]), transmit clock
(TXCLK), transmit enable (TXEN), transmit error (TXER), four receive
data bits (RXD[3:0]), receive clock (RXCLK), carrier sense (CRS),
receive data valid (RXDV), receive data error (RXER), and collision
(COL). The transmit clock (TXCLK) is a common signal for all four
channels. All other signals are separate for each channel. The transmit
and receive clocks operate at 25 MHz in 100 Mbps mode.
On the transmit side, the TXCLK output runs continuously at 25 MHz.
When no data is to be transmitted, TXEN must be deasserted. While
TXEN is deasserted, TXER and TXD[3:0] are ignored and no data is
clocked into the device. When TXEN is asserted on the rising edge of
TXCLK, data on TXD[3:0] is clocked into the device on rising edges of
the TXCLK output clock. TXD[3:0] input data is nibble wide packet data
whose format is specified in IEEE 802.3 and shown in Figure 3. When
all packet data has been latched into the device, TXEN must be
deasserted on the rising edge of TXCLK.
TXER is also clocked in on rising edges of the TXCLK clock. TXER is a
transmit error signal which, when asserted, will substitute an error nibble
in place of the normal data nibble that was clocked in on the TXD[3:0]
nibble at the same time as the TXER assertion. The error nibble is the
/H/ symbol, as defined in IEEE 802.3 and shown in Table 3.
Since CLKIN (input clock) generates TXCLK (output clock), TXD[3:0],
TXEN, and TXER are also clocked in on the rising edges of CLKIN.
On the receive side, as long as a valid data packet is not detected, CRS
and RXDV are deasserted and RXD[3:0] is held low. When the start of
packet is detected, CRS is asserted on the falling edge of RXCLK. The
assertion of RXDV indicates that valid data is available on RXD[3:0].
Data may be externally latched using the rising edge of RXCLK. The
RXD[3:0] data has the same frame structure as the TXD[3:0] data,
specified in IEEE 802.3 and shown in Figure 3. When the end of packet
is detected, CRS and RXDV are deasserted, and RXD[3:0] is held low.
CRS and RXDV also stay deasserted if the channel is in Link Fail state.
RXER is a receive error output that is asserted when certain errors are
detected on a data nibble. RXER is asserted on the falling edge of
RXCLK for the duration of the RXCLK clock cycle during which the nibble
containing the error is output on RXD[3:0].
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The collision output, COL, is asserted whenever the collision condition is
detected.
2.2.3 MII - 10Mbps
10 Mbps operation is identical to the 100 Mbps operation, except:
•
TXCLK and RXCLK clock frequency is 2.5 MHz.
TXER is ignored.
•
•
•
RXER is disabled and always held low.
Receive operation is modified as follows. On the receive side, when
the squelch circuit determines that invalid data is present on the TP
(Twisted Pair) inputs, the receiver is idle. During idle, RXCLK follows
TXCLK, RXD[3:0] is held low, and CRS and RXDV are deasserted.
When a start of packet is detected on the TP receive inputs, CRS is
asserted and the clock recovery process starts on the incoming TP
input data. After the receive clock has been recovered from the data,
the RXCLK is switched over to the recovered clock output and the
data valid signal RXDV is asserted on a falling edge of RXCLK. Once
RXDV is asserted, valid data is clocked out on RXD[3:0] on falling
edges of the RXCLK clock. The RXD[3:0] data has the same packet
structure as the TXD[3:0] data and is formatted as specified in IEEE
802.3 and shown in Figure 3. When the end of packet is detected,
CRS and RXDV are deasserted. CRS and RXDV also stay
deasserted as long as the channel is in the Link Fail State.
2.2.4 RMII - 100 Mbps
The RMII is a reduced pin count version of the MII defined by an industry
group, the RMII Consortium. The RMII is a two-bit-wide packet data
interface that operates at 50 Mhz. The L84225 meets all the RMII
requirements outlined in the RMII Consortium specifications and can
directly connect to any Ethernet controller that also complies with the
RMII specifications.
The RMII is similar to the MII, except:
•
•
The data path is two bits wide instead of four.
Transmit and receive data is passed over TXD[1:0] and RXD[1:0]
pins, respectively.
Functional Description
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•
•
The CLKIN clock frequency must be 50 MHz instead of 25 MHz.
All timing for both transmit and receive is referenced to a single clock
on CLKIN instead of TXCLK for transmit and RXCLK for receive.
•
An elastic buffer is present in the receive data path to account for
any difference between the CLKIN and receive data frequencies. The
elastic buffer is 32 bits in length. Input data from the receiver fills the
buffer to a predetermined threshold level before data is passed to the
RMII outputs. This threshold level can be configured to either 4 bits
or 16 bits by appropriately setting the RMII threshold select bit in the
MI serial port Global Configuration register.
•
The MII RXDV and CRS inputs are combined into one signal that is
outputted on the CRS pin. CRS is asserted active high when
incoming packet data is detected on the receive inputs. It stays
asserted high until packet data is no longer detected, and it toggles
at a 25 MHz rate (low for first di-bit of MII nibble, high for second,
etc.) from the end of the packet data detection until end of valid data
transfer from the elastic buffer. During this toggling interval, valid data
is still being output on RXD[1:0]. CRS is finally deasserted when all
data has been output from the internal elastic buffer on RXD[1:0].
•
•
•
RXD[1:0]=00 from start of CRS until valid data is ready to be output.
TXEN to CRS loopback is disabled.
Any packet that contains an error will assert RXER and substitute
RXD[1:0]=10 for all the data bits from the error detect point until the
end of packet.
2.2.5 RMII - 10 Mbps
10 Mbps RMII operation is identical to 100 Mbps RMII operation, except:
•
•
•
The CLKIN frequency remains at 50 Mhz (same as 100 Mbps
operation).
Each data di-bit must be input on TXD[1:0] for ten consecutive
CLKIN cycles.
Each data di-bit will be output on RXD[1:0] for ten consecutive
CLKIN cycles.
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2.2.6 FBI - 100 Mbps
The Five Bit Interface (FBI), or Symbol Interface, is a five bit wide
interface produced when the 4B5B encoder/ decoder is bypassed. The
FBI is primarily used for repeaters or Ethernet controllers that have
integrated encoder/decoders.
The FBI is identical to the MII, except:
•
•
•
•
The FBI data path is five bits wide, not nibble wide like the MII.
TXER pin is changed to be the fifth transmit data bit, TXD4.
RXER pin is changed to be the fifth receive data bit, RXD4.
CRS is asserted as long as the device is in the Link Pass state (CRS
no longer asserted/deasserted at beginning/end of packet).
•
•
•
COL is not valid.
RXDV is not valid.
TXEN is ignored.
2.2.7 FBI - 10 Mbps
The FBI is not available in 10 Mbps mode.
2.2.8 Selection of MII, RMII, or FBI
MII is the default interface to the MAC controller. RMII is selected by
asserting the RMII_EN pin, a global control.
The FBI is automatically enabled when the 4B5B encoder/ decoder is
bypassed. Bypassing the encoder/decoder passes the 5B symbols
between the receiver/transmitter directly to the FBI without any alteration
or substitutions. The 4B5B encoder/decoder can be bypassed by setting
the bypass encoder bit in the MI serial port Channel Configuration
register.
When the FBI is enabled, it may also be desirable to bypass the
scrambler/descrambler and disable the internal CRS loopback function.
The scrambler/ descrambler can be bypassed by setting the bypass
scrambler bit in the MI serial port Channel Configuration register. The
internal CRS loopback can be disabled by setting the TXEN to CRS
loopback disable bit in the MI serial port Channel Configuration register.
Functional Description
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2.2.9 MII Disable
The MII and FBI inputs and outputs can be disabled by setting the MII
disable bit in the MI serial port Control register. When the MII is disabled,
the inputs are ignored, the outputs are placed in high impedance state,
and the TP output is high impedance.
2.2.10 TXEN to CRS Loopback Disable
The internal TXEN to CRS loopback can be disabled by appropriately
setting the TXEN to CRS loopback disable bit in the MI serial port
Channel Configuration register. TXEN to CRS loopback is disabled in
RMII mode.
2.3 Encoder
2.3.1 4B5B Encoder - 100 Mbps
100BaseTX and 100BaseFX require that the data be 4B5B encoded.
4B5B coding converts the 4-bit data nibbles into 5-bit data words. The
mapping of the 4B nibbles to the 5B code words is specified in IEEE
802.3 and shown in Table 3. The 4B5B encoder on the L84225 takes 4B
nibbles from the controller interface, converts them into 5B words
according to Table 3, and sends the 5B words to the scrambler. The
4B5B encoder also substitutes the first eight bits of the preamble with the
SSD delimiters (/J/K/ symbols) and adds an ESD delimiter (/T/R/
symbols) to the end of each packet, as defined in IEEE 802.3 and shown
in Figure 2. The 4B5B encoder also fills the period between packets,
called the idle period, with a continuous stream of idle symbols, as
shown in Figure 2.
Table 3
4B/5B Symbol Mapping
Symbol Name
Description
5B Code
4B Code
0
1
2
3
4
Data 0
Data 1
Data 2
Data 3
Data 4
11110
01001
10100
10101
01010
0000
0001
0010
0011
0100
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Table 3
4B/5B Symbol Mapping (Cont.)
Symbol Name
Description
5B Code
4B Code
5
6
Data 5
Data 6
Data 7
Data 8
Data 9
Data A
Data B
Data C
Data D
Data E
Data F
01011
01110
01111
10010
10011
10110
10111
11010
11011
11100
11101
0101
0110
0111
1000
1001
1010
1011
1100
1101
1110
1111
7
8
9
A
B
C
D
E
F
I
Idle
11111
0000
J
K
T
R
H
SSD #1
SSD #2
ESD #1
ESD #2
Halt
11000
10001
01101
00111
00100
0101
0101
0000
0000
Undefined
---
Invalid codes
All others1
00001
1. These 5B codes are not used. For decoder, these 5B codes are
decoded to 4B 0000. For encoder, 4B 0000 is encoded to 5B
11110, as shown in symbol Data 0.
Functional Description
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2.3.2 Manchester Encoder - 10 Mbps
The Manchester encoding process combines clock and NRZ data such
that the first half of the data bit contains the complement of the data, and
the second half of the data bit contains the true data, as specified in
IEEE 802.3. This guarantees that a transition always occurs in the middle
of the bit cell. The L84225 Manchester encoder converts the 10 Mbps
NRZ data from the controller interface into a single data stream for the
TP transmitter and adds a start of idle pulse (SOI) at the end of the
packet as specified in IEEE 802.3 and shown in Figure 2. The
Manchester encoding process is only done on actual packet data, and
the idle period between packets is not Manchester encoded, but filled
with link pulses.
2.3.3 Encoder Bypass
The 4B5B encoder can be bypassed by setting the bypass
encoder/decoder bit in the MI serial port Channel Configuration register.
When this bit is set to bypass the encoder/decoder, 5B code words are
passed directly from the controller interface to the scrambler without any
alterations. Setting this bit automatically places the device in the FBI
mode, as described in Section 2.2, “Controller Interface,” page 16.
2.4 Decoder
2.4.1 4B5B Decoder - 100 Mbps
Since the FX or TX input data is 4B5B encoded on the transmit side, it
must also be decoded by the 4B5B decoder on the receive side. The
mapping of the 5B nibbles to the 4B code words is specified in IEEE
802.3 and shown in Table 3. The L84225 4B5B decoder takes the 5B
code words from the descrambler, converts them into 4B nibbles per
Table 3, and sends the 4B nibbles to the controller interface. The 4B5B
decoder also strips off the SSD delimiter (/J/K/ symbols) and replaces
them with two 4B Data 5 nibbles (/5/ symbol), and strips off the ESD
delimiter (/T/R/ symbols) and replaces it with two 4B Data 0 nibbles (/I/
symbol), per IEEE 802.3 specifications and shown in Figure 2.
The 4B5B decoder detects SSD, ESD and, codeword errors in the
incoming data stream as specified in IEEE 802.3. These errors are
indicated by asserting RXER output while the errors are being
transmitted across RXD[3:0], and they are also indicated by setting SSD,
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ESD, and codeword error bits in the MI serial port Channel Status Output
register.
2.4.2 Manchester Decoder - 10 Mbps
In Manchester coded data, the first half of the data bit contains the
complement of the data, and the second half of the data bit contains the
true data. The L84225 Manchester decoder converts the single data
stream from the TP receiver into NRZ data for the controller interface by
decoding the data and stripping off the SOI pulse. Since the clock and
data recovery block has already separated the clock and data from the
TP receiver, the Manchester decoding process to NRZ data is inherently
performed by that block.
2.4.3 Decoder Bypass
The 4B5B decoder can be bypassed by setting the bypass
encoder/decoder bit in the MI serial port Channel Configuration register.
When this bit is set to bypass the encoder/decoder:
•
•
5B code words are passed directly to the controller interface from the
descrambler without any alterations.
CRS is asserted whenever the device is in the Link Pass state.
2.5 Clock and Data Recovery
2.5.1 Clock Recovery - 100 Mbps
Clock recovery is done with a PLL. If there is no valid data present on
the receive inputs, the PLL is locked to the 25 MHz TXCLK. When valid
data is detected on the receive inputs with the squelch circuit and when
the adaptive equalizer has settled, the PLL input is switched to the
incoming data stream. The PLL then recovers a clock by locking onto the
transitions of the incoming signal. The recovered clock frequency is a 25
MHz nibble clock, and that clock is output as the controller interface
signal RXCLK.
For FX operation, when the SD pin is asserted, the PLL input is switched
to the incoming data on the input.
Functional Description
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2.5.2 Data Recovery - 100 Mbps
Data recovery is performed by latching in data from the receive inputs
with the recovered clock extracted by the PLL. The data is then
converted from a single bit stream into a nibble widedone by latching in
valid data from the receiver with the recovered clock extracted by the
PLL. The data is then converted from a single bit stream into a nibble-
wide data word.
2.5.3 Clock Recovery - 10 Mbps
The clock recovery process for 10 Mbps mode is identical to the 100
Mbps mode, except:
•
•
The recovered clock frequency is a 2.5 MHz nibble clock.
The PLL is switched from TXCLK to the TP input when the squelch
indicates valid data.
•
•
The PLL locks onto the preamble signal in less than 12 transitions
(bit times).
Some of the preamble data symbols are lost while the PLL is locking
onto the preamble. However, the data receiver block recovers
enough preamble symbols to pass at least 6 nibbles of preamble to
the controller interface, as shown in Figure 3.
2.5.4 Data Recovery
The data recovery process for 10 Mbps mode is identical to the 100
Mbps mode, except, the recovered clock frequency is a 2.5 MHz nibble
clock. As mentioned in Section 2.4.2, “Manchester Decoder - 10 Mbps,”
page 25, the data recovery process inherently performs decoding of
Manchester encoded data from the TP inputs.
2.6 Scrambler
2.6.1 100 Mbps
100BaseTX requires scrambling to reduce the radiated emissions on the
twisted pair. The L84225 scrambler takes the encoded data from the
4B5B encoder, scrambles it per the IEEE 802.3 specifications, and sends
it to the TP transmitter. The scrambler circuitry of the L84225 is designed
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so that none of the individual scrambler sections on-chip will be
synchronous with the others to minimize EMI issues.
2.6.2 10 Mbps
A scrambler is not used in 10 Mbps mode.
2.6.3 Scrambler Bypass
The scrambler can be bypassed by setting the bypass
scrambler/descrambler bit in the MI serial port Channel Configuration
register. When this bit is set, the 5B data bypasses the scrambler and
goes directly from the 4B5B encoder to the twisted pair transmitter.
2.7 Descrambler
2.7.1 100 Mbps
The L84225 descrambler takes the scrambled data from the data
recovery block, descrambles it per the IEEE 802.3 specifications, aligns
the data on the correct 5B word boundaries, and sends it to the 4B5B
decoder.
The algorithm for synchronization of the descrambler is the same as the
algorithm outlined in the IEEE 802.3 specification. Once the descrambler
is synchronized, it will maintain synchronization as long as enough
descrambled idle pattern 1’s are detected within a given interval. To stay
in synchronization, the descrambler needs to detect at least 25
consecutive descrambled idle pattern 1’s in a 1 ms interval. If 25
consecutive descrambled idle pattern 1’s are not detected within the 1
ms interval, the descrambler goes out of synchronization and restarts the
synchronization process.
If the descrambler is in the unsynchronized state, the descrambler loss
of synchronization detect bit is set in the MI serial port Channel Status
Output register to indicate this condition. Once this bit is set, then it will
stay set until the descrambler achieves synchronization.
A descrambler is not used for FX operation.
Functional Description
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2.7.2 10 Mbps
A descrambler is not used in 10 Mbps mode.
2.7.3 Descrambler Bypass
The descrambler can be bypassed by setting the bypass
scrambler/descrambler bit in the MI serial port Channel Configuration
register. When this bit is set, the data bypasses the descrambler and
goes directly from the TP receiver to the 4B5B decoder.
2.8 Twisted Pair Transmitter
2.8.1 100 Mbps
The TP transmitter consists of an MLT3 encoder, waveform generator,
and line driver.
The MLT3 encoder converts the NRZI data from the scrambler into a
three level code required by IEEE 802.3. MLT3 coding uses three levels
and converts 1's to transitions between the three levels, and converts 0's
to no transitions or changes in level.
The purpose of the waveform generator is to shape the transmit output
pulse. The waveform generator takes the MLT3 three level encoded
waveform and uses an array of switched current sources to control the
shape of the twisted pair output signal in order to meet IEEE 802.3
requirements. The output of the switched current sources then goes
through a low pass filter in order to "smooth" the output and remove any
high frequency components. In this way, the waveform generator pre-
shapes the output waveform transmitted onto the twisted pair cable to
meet the pulse template requirements outlined in IEEE 802.3. The
waveform generator eliminates the need for any external filters on the TP
transmit output. The line driver converts the shaped and smoothed
waveform to a current output that can drive 100 meters of category 5
unshielded twisted pair cable or 150 ohm shielded twisted pair cable.
2.8.2 10 Mbps
The TP transmitter operation in 10 Mbps mode is much different from the
100 Mbps transmitter. Even so, the transmitter still consists of a
waveform generator and line driver.
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The purpose of the waveform generator is to shape the output transmit
pulse. The waveform generator consists of a ROM, DAC, clock generator,
and filter. The DAC generates a stair-stepped representation of the
desired output waveform. The stairstepped DAC output then goes
through a low pass filter in order to "smooth" the DAC output and remove
any high frequency components. The DAC values are determined from
the ROM output; the ROM outputs are chosen to shape the pulse to the
desired template and are clocked into the DAC at high speed by the clock
generator. In this way, the waveform generator pre-shapes the output
waveform to be transmitted onto the twisted pair cable to meet the pulse
template requirements outlined in IEEE 802.3 Clause 14 and also shown
in Figure 4. The waveshaper replaces and eliminates external filters on
the TP transmit output.
The line driver converts the shaped and smoothed waveform to a current
output that can drive 100 meters of category 3/4/5 100 Ohm unshielded
twisted pair cable or 150 Ohm shielded twisted pair cable, without any
external filters. During the idle period, no output signal is transmitted on
the TP outputs (except link pulse).
2.9 Twisted Pair Receiver
2.9.1 Receiver - 100 Mbps
The TP receiver detects input signals from the twisted pair input and
converts it to a digital data bit stream ready for clock and data recovery.
The receiver can reliably detect data from a 100Base-TX compliant
transmitter that has been passed through 0-100 meters of 100-Ohm
category 5 UTP.
The 100 Mbps receiver consists of an adaptive equalizer, baseline
wander correction circuit, comparators, and MLT- 3 decoder. The TP
inputs first go to an adaptive equalizer. The adaptive equalizer
compensates for the low pass characteristic of the cable, and it has the
ability to adapt and compensate for 0-100 meters of category 5, 100
Ohm UTP. The baseline wander correction circuit restores the DC
component of the input waveform that was removed by external
transformers. The comparators convert the equalized signal back to
digital levels and are used to qualify the data with the squelch circuit. The
MLT-3 decoder takes the three level MLT-3 digital data from the
Functional Description
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comparators and converts it back to normal digital data to be used for
clock and data recovery.
Figure 4
TP Output Voltage Template
B
N
1.0
0.8
0.6
0.4
0.2
P
H
I
O
D
E
C
Q
R
0.0
- 0.2
- 0.4
- 0.6
- 0.8
- 1.0
A
M
J
F
S
U
L K
W
V
T
G
0
10
20
30
40
50
60
70
80
90
100
110
Time (ns)
Time (ns)
Internal MAU
Time (ns)
Internal MAU Voltage (V)
Reference
Voltage (V)
Reference
A
B
C
D
E
F
G
H
I
0
0
1.0
0.4
0.55
0.45
0
M
N
O
P
61
0
15
15
25
32
39
57
48
67
89
74
73
85
1.0
100
110
111
111
111
110
100
110
90
0.4
0.75
0.15
0
Q
R
S
-1.0
0.7
0.6
0
-0.15
-1.0
-0.3
-0.7
-0.7
T
U
V
J
K
L
-0.55
-0.55
W
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2.9.2 Receiver - 10 Mbps
The 10 Mbps mode receiver is much simpler than the 100 Mbps mode
receiver and is identical to the 100 Mbps receiver except:
•
•
•
The adaptive equalizer is disabled and bypassed.
The baseline wander correction circuit is disabled.
The 10 Mbps receiver is able to detect input signals from the twisted
pair cable that are within the template specified in IEEE 802.3 Clause
14 and shown in Figure 5.
•
•
The output of the squelch comparator is used for squelch, link pulse
detect, SOI detect, reverse polarity detect.
The data comparator is a zero crossing comparator whose output is
used for clock and data recovery.
2.9.3 Squelch - 100 Mbps
The squelch block determines whether the input contains valid data. The
100 Mbps TX squelch is one of the criteria used to determine link
integrity. The squelch comparators compare the TX inputs against fixed
positive and negative thresholds, called squelch levels.
The output from the squelch comparator goes to a digital squelch circuit,
which determines whether the receive input data on that channel is valid.
If the data is invalid, the receiver is in the squelched state. If the input
voltage exceeds the squelch levels at least four times with alternating
polarity within a 10 us interval, the data is considered to be valid by the
squelch circuit and the receiver now enters into the unsquelch state.
Functional Description
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Figure 5
TP Input Voltage Template - 10 Mbps
a. Short Bit
3.1 V
Slope 0.5 V/ns
585 mV
585 mV sin (π t/PW)
0
PW
b. Long Bit
3.1 V
Slope 0.5 V/ns
585 mV
585 mV sin (π t/PW)
585 mV sin [2 π (t − PW2)/PW]
PW/4 3PW/4
0
PW
In the unsquelch state, the receive threshold level is reduced by
approximately 30% for noise immunity reasons and is called the
unsquelch level. When the receiver is in the unsquelch state the input
signal is considered valid.
The device stays in the unsquelch state until loss of data is detected.
Loss of data is detected if no alternating polarity unsquelch transitions
are detected during any 10 us interval. When the loss of data is detected,
the receive squelch level is re-established.
2.9.4 Squelch - 10 Mbps
The TP squelch algorithm for 10 Mbps mode is identical to the 100 Mbps
mode, except:
•
The 10 Mbps squelch algorithm is not used for link integrity, but to
sense the beginning of a packet.
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•
The receiver goes into the unsquelch state if the input voltage
exceeds the squelch levels for three bit times with alternating polarity
within a 50-250 ns interval.
•
•
The receiver goes into the squelch state when SOI is detected.
Unsquelch detection has no affect on link integrity, link pulses are
used for that in 10 Mbps mode.
•
•
Start of packet is determined when the receiver goes into the
unsquelch state and CRS is asserted.
The receiver meets the squelch requirements defined in IEEE 802.3
Clause 14.
2.9.5 Receive Level Adjust
The receiver squelch and unsquelch levels can be lowered by 4.5 dB by
setting the receive level adjust bit in the MI serial port Channel
Configuration register. By setting this bit, the device can support cable
lengths exceeding 100 meters.
2.10 Fiber Interface
2.10.1 General
The Fiber Interface implements the 100BaseFX function defined in IEEE
802.3.
The Fiber Interface consists of three signals: (1) a differential PECL data
output (FXOP/FXON), (2) a differential PECL data input (FXIP/FXIN),
and (3) a PECL signal detect (SD/FXEN).
The Fiber Interface section consists of four blocks: (1) transmitter, (2)
receiver, (3) signal detect, and (4) far end fault.
The Fiber Interface can be independently selected for each channel with
the SD/FXEN_[3:0] pins.
The Fiber Interface is disabled in 10Mbps mode. AutoNegotiation and the
scrambler/descrambler are disabled when the Fiber Interface is enabled.
The Fiber Interface meets all IEEE 802.3 requirements.
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2.10.2 Transmitter
The FX transmitter converts data from the 4B5B encoder into binary
NRZI data and outputs the data onto the FXOP/FXON pins for each
channel. The output driver is a differential current source that will drive a
100-ohm load to ECL levels. The FXOP/FXON pins can directly drive an
external fiber optic transceiver. The FX transmitter meets all the
requirements defined in IEEE 802.3.
The FX transmit output current level is derived from an internal reference
voltage and the external resistor on REXT pin.
2.10.3 Receiver
The FX receiver (1) converts the differential ECL inputs on the
FXIP/FXIN pins for each channel to a digital bit stream, (2) validates the
data on FXIP/FXIN with the SD/ FXEN input pin for each channel, and
(3) enable/disables the Fiber Interface with the SD/FXEN pin for each
channel. The FX receiver meets all requirements defined in IEEE 802.3.
The input to the FXIP/FXIN pins can be directly driven from a fiber optic
transceiver and first goes to a comparator. The comparator compares the
input waveform against the internal ECL threshold levels to produce a
low jitter serial bit stream with internal logic levels. The data from the
comparator output is then passed to the clock and data recovery block
provided the signal detect input, SD/FXEN, is asserted. The signal detect
function is described in the next section.
2.10.4 Signal Detect
The FX receiver has a signal detect input pin, SD/FXEN, for each
channel which indicates whether the incoming data on FXIP/FXIN is valid
or not for that channel. The SD/FXEN pin can be driven directly from an
external fiber optic transceiver and meets all requirements defined in the
IEEE 802.3 specifications.
The SD/FXEN input goes directly to a comparator. The comparator
compares the input waveform against the internal ECL threshold level to
produce a digital signal with internal logic levels. The output of the signal
detect comparator then goes to the link integrity and squelch blocks. If
the signal detect input is asserted, the channel is placed in the Link Pass
state and the input data on FXIP/FXIN is determined to be valid. If the
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signal detect input is deasserted, the channel is placed in the Link Fail
state and the input data on FXIP/FXIN is determined to be invalid.
The SD_THR pin adjusts the ECL trip point of the SD/ FXEN input. When
the SD_THR pin is tied to a voltage between GND and GND+0.45V, the
trip point of the SD ECL input buffer is internally set to VCC-1.3V. When
SD_THR pin is set to a voltage greater than GND+0.85v, the trip point
of the SD SD/FXEN ECL input buffer is set to the voltage that is applied
to the SD_THR pin. The trip level for the SD/FXEN input buffer must be
set to VCC- 1.3V. Having external control of the SD/FXEN buffer trip level
with the SD_THR pin allows this trip level to be referenced to an external
supply which facilitates connection to both 3.3V and 5V external fiber
optic transceiver. If the device is to be connected to a 3.3V external fiber
optic transceiver, then SD_THR should be tied to GND. If the device is
to be connected to a 5V external fiber optic transceiver, then SD_THR
needs to be tied to VCC-1.3V, and this can be done so with an external
resistor divider. Refer to Section 4, “Application Information,” page 70, for
more details on connections to external fiber optic transceivers.
2.10.5 Fiber Interface Disable
The Fiber Interface will be disabled if the SD/FXEN pin is tied to GND.
Disabling the Fiber Interface automatically enables the TP interface.
2.10.6 Far End Fault
Each channel has the Far End Fault capability, referred to as FEF, and
defined in IEEE 802.3 specifications. FEF is a method by which the Fiber
Interface can signal a fault to a remote device by transmitting an idle
pattern consisting of 84 ‘1’s followed by a single ‘0’ repeatedly (idle
period normally has all 1’s). FEF was specified in IEEE 802.3 because
FX lacks the AutoNegotiation capability to signal a remote fault to
another station.
FEF can only be made operational only when the Fiber Interface is
enabled. In the device default state with the Fiber Interface enabled, FEF
is disabled, but it can be enabled by setting the FEF select bit in the MI
serial port Global Configuration register. When FEF is enabled, (1) a ‘0’
is transmitted after each group of 84 ‘1’s repeatedly during idle if the
SD/FXEN pin is deasserted, and (2) if an FEF stream is detected by the
receiver for 3 consecutive intervals, the remote fault bit is set in the MI
serial port Status register and the LED0 output pin is asserted.
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2.11 Collision
2.11.1 100 Mbps
Collision occurs whenever transmit and receive occur simultaneously
while the device is in Half Duplex. Collision is sensed whenever there is
simultaneous transmission (packet transmission on TPOP/N) and
reception (non-idle symbols detected on receive input). When collision is
detected:
•
•
•
•
The COL output is asserted.
TP data continues to be transmitted on twisted pair outputs.
TP data continues to be received on twisted pair inputs.
Internal CRS loopback is disabled.
Once collision starts, CRS is asserted and stays asserted until the
receive and transmit packets that caused the collision are terminated.
The collision function is disabled if the device is in the Full Duplex mode,
is in the Link Fail state, or if the device is in the diagnostic loopback
mode.
2.11.2 10 Mbps
Collision in 10 Mbps mode is identical to the 100 Mbps mode, except:
•
•
•
•
Reception is determined by the 10 Mbps squelch criteria.
RXD[3:0] outputs are forced to all 0's.
Collision is asserted when the SQE test is performed.
Collision is asserted when the jabber condition has been detected.
2.11.3 Collision Test
The controller interface collision signal, COL, can be tested by setting the
collision test register bit in the MI serial port Control register. When this
bit is set, TXEN is looped back onto COL and the TP outputs are
disabled.
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2.11.4 Collision Indication
Collision can be programmed to appear on the LED2 pin by appropriately
setting the LED definition bits in the MI serial port Global Configuration
register. Section 2.23, “LED Drivers,” page 48, describes the
programmable LED definition bit settings. When the LED2 pin is
programmed to be a collision detect output, the pin is asserted low for
100 ms every time a collision occurs.
2.12 Start of Packet
2.12.1 100 Mbps
Start of packet for 100 Mbps mode is indicated by a unique Start of
Stream Delimiter (SSD). The SSD pattern consists of the two /J/K/ 5B
symbols inserted at the beginning of the packet in place of the first two
preamble symbols, as defined in IEEE 802.3 Clause 24 and shown in
Table 3 and Figure 2.
The transmit SSD is generated by the 4B5B encoder and the /J/K/
symbols are inserted by the 4B5B encoder at the beginning of the
transmit data packet in place of the first two 5B symbols of the preamble,
as shown in Figure 2.
The receive pattern is detected by the 4B5B decoder by examining
groups of 10 consecutive code bits (two 5B words) from the descrambler.
Between packets, the receiver will be detecting the idle pattern, which is
5B /I/ symbols. While in the idle state, CRS and RXDV are deasserted.
If the receiver is in the idle state and 10 consecutive code bits from the
receiver consist of the /J/K/ symbols, the start of packet is detected, data
reception is begun, CRS and RXDV are asserted, and /5/5/ symbols are
substituted in place of the /J/K/ symbols.
If the receiver is in the idle state and 10 consecutive code bits from the
receiver consist of a pattern that is neither /I/ I/ nor /J/K/ symbols but
contains at least 2 non-contiguous 0's, then activity is detected but the
start of packet is considered to be faulty and a False Carrier Indication
(also referred to as bad SSD) is signaled to the controller interface. When
False Carrier is detected CRS is asserted, RXDV remains deasserted,
RXD[3:0]=1110 while RXER is asserted, and the bad SSD bit is set in
the MI serial port Channel Status Output register. Once a False Carrier
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Event is detected, the idle pattern (two /I/I/ symbols) must be detected
before any new SSD’s can be sensed.
If the receiver is in the idle state and 10 consecutive code bits from the
receiver consist of a pattern that is neither /I/ I/ nor /J/K/ symbols but
does not contain at least 2 non contiguous 0's, the data is ignored and
the receiver stays in the idle state.
2.12.2 10 Mbps
Since the idle period in 10 Mbps mode is defined to be no data on the
TP inputs, then the start of packet for 10 Mbps mode is detected when
valid data is detected by the TP squelch circuit. When start of packet is
detected, CRS is asserted as described in Section 2.2, “Controller
Interface,” page 16. Refer to Section 2.9.4, “Squelch - 10 Mbps,” page 32,
for the algorithm for valid data detection.
2.13 End of Packet
2.13.1 100 Mbps
End of packet for 100 Mbps mode is indicated by an End of Stream
Delimiter (referred to as ESD). The ESD pattern consists of the two /T/R/
4B5B symbols inserted after the end of the packet, as defined in IEEE
802.3 Clause 24 and shown in Table 3 and Figure 2.
The transmit ESD is generated by the 4B5B encoder and the /T/R/
symbols are inserted by the 4B5B encoder after the end of the transmit
data packet, as shown in Figure 2.
The receive ESD pattern is detected by the 4B5B decoder by examining
groups of 10 consecutive code bits (two 5B words) from the descrambler
during valid packet reception to determine whether there is an ESD.
If the 10 consecutive code bits from the receiver during valid packet
reception consist of the /T/R/ symbols, the end of packet is detected,
data reception is terminated, CRS and RXDV are deasserted, and /I/I/
symbols are substituted in place of the /T/R/ symbols.
If 10 consecutive code bits from the receiver during valid packet
reception do not consist of /T/R/ symbols, but consist of /I/I/ symbols
instead, the packet is considered to have been terminated prematurely
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and abnormally. When this premature end of packet condition is
detected, RXER remains asserted for the nibble associated with the first
/I/ symbol detected and then RXER and CRS and RXDV are all
deasserted. Premature end of packet condition is also indicated by
setting the ESD error bit in the MI serial port Channel Status Output
register.
2.13.2 10 Mbps
The end of packet for 10 Mbps mode is indicated with the SOI (Start of
Idle) pulse. The SOI pulse is a positive double wide pulse containing a
Manchester code violation inserted at the end of every packet.
The transmit SOI pulse is generated by the TP transmitter and inserted
at the end of the data packet after TXEN is deasserted. The transmitted
SOI output pulse at the TP output is shaped by the transmit waveshaper
to meet the pulse template requirements specified in IEEE 802.3 Clause
14 and shown in Figure 6.
The receive SOI pulse is detected by the TP receiver by sensing missing
data transitions. Once the SOI pulse is detected, data reception is ended
and CRS and RXDV are deasserted.
Figure 6
SOI Output Voltage Template - 10 Mbps
0 BT
4.5 BT
3.1 V
0.5 V/ns
0.25 BT
2.25 BT
6.0 BT
585 mV
+50 mV
−50 mV
585 mV sin (2
π
(t/1 BT))
45.0 BT
0 ≤ t ≤ 0.25 BT and
2.25 ≤ t ≤ 2.5 BT
−3.1 V
2.5 BT 4.5 BT
Functional Description
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Figure 7
Link Pulse Output Voltage Template - 10 Mbps
1.3 BT
0 BT
3.1 V
0.5 V/ns
0.5 BT
585 mV
0.6 BT
2.0 BT
300 mV
4.0 BT
+50 mV
+50 mV
−50 mV
200 mV
−50 mV
42.0 BT
4.0 BT
0.25 BT
−3.1 V
0.85 BT 2.0 BT
2.14 Link Integrity and AutoNegotiation
2.14.1 General
The L84225 can be configured to implement either the standard link
integrity algorithms or the AutoNegotiation algorithm.
The standard link integrity algorithms are used solely to establish an
active link to and from a remote device. There are different standard link
integrity algorithms for 10 and 100 Mbps modes. The AutoNegotiation
algorithm is used for two purposes:
•
•
To automatically configure the device for either 10/100 Mbps and
Half/Full Duplex modes
To establish an active link to and from a remote device
The standard link integrity and AutoNegotiation algorithms are described
below.
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2.14.2 10Base-T Link Integrity Algorithm
The L84225 uses the same 10Base-T link integrity algorithm that is
defined in IEEE 802.3 clause 14. This algorithm uses normal link pulses,
referred to as NLP’s and transmitted during idle periods, to determine if
a device has successfully established a link with a remote device (called
Link Pass state). The transmit link pulse meets the template defined in
IEEE 802.3 Clause 14 and shown in Figure 7. Refer to IEEE 802.3
Clause 14 for more details if needed.
2.14.3 100Base-TX Link Integrity Algorithm
Since 100Base-TX is defined to have an active idle signal, then there is
no need to have separate link pulses like those defined for 10Base-T.
The L84225 uses the squelch criteria and descrambler synchronization
algorithm on the input data to determine if the device has successfully
established a link with a remote device (called Link Pass state). Refer to
IEEE 802.3 for details on both algorithms.
2.14.4 AutoNegotiation Algorithm
As stated previously, the AutoNegotiation algorithm is used for two
purposes:
•
•
To automatically configure the device for either 10/100 Mbps and
Half/Full Duplex modes
To establish an active link to and from a remote device
The AutoNegotiation algorithm is the same algorithm that is defined in
IEEE 802.3 Clause 28. AutoNegotiation uses a burst of link pulses, called
fast link pulses and referred to as FLP’s, to pass up to 16 bits of signaling
back and forth between the L84225 and a remote device. The transmit
FLP pulses meet the template specified in IEEE 802.3 and shown in
Figure 7. A timing diagram contrasting NLP’s and FLP’s is shown in
Figure 8.
Functional Description
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Figure 8
NLP vs. FLP Link Pulse
a. Normal Link Pulse (NLP)
TX_DI±
b. Fast Link Pulse (FLP)
TX_DI±
D0
D1
D2
D3
D14 D15
Clock Clock Clock Clock Clock Clock Clock
Data Data Data Data Data Data
The AutoNegotiation algorithm is initiated by any of the following events:
•
•
•
•
Powerup
Device Reset
AutoNegotiation Reset
Entering the Link Fail state
Once a negotiation has been initiated, the L84225 first determines if the
remote device has AutoNegotiation capability. If the device is not
AutoNegotiation capable and is just transmitting either a 10Base-T or
100Base-TX signal, the L84225 will sense that and place itself in the
correct mode. If the L84225 detects FLP’s from the remote device, then
the remote device is determined to have AutoNegotiation capability and
the device then uses the contents of the MI serial port AutoNegotiation
Advertisement register and FLP’s to advertise it’s capabilities to a remote
device. The remote device does the same, and the capabilities read back
from the remote device are stored in the MI serial port AutoNegotiation
Remote End Capability register. The L84225 negotiation algorithm then
matches it’s capabilities to the remote devices capabilities and
determines to what mode the device should be configured according to
the priority resolution algorithm defined in IEEE 802.3 Clause 28. Once
the negotiation process is completed, the L84225 then configures itself
for either 10 or 100 Mbps mode and either Full or Half Duplex modes
(depending on the outcome of the negotiation process), and it switches
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to either the 100Base-TX or 10Base-T link integrity algorithms
(depending on which mode was enabled by AutoNegotiation). Refer to
IEEE 802.3 Clause 28 for more details.
2.14.5 AutoNegotiation Outcome Indication
The outcome or result of the AutoNegotiation process is stored in the
speed detect and duplex detect bits in the MI serial port Status Output
register.
2.14.6 AutoNegotiation Status
The status of the AutoNegotiation process can be monitored by reading
the AutoNegotiation Acknowledgement Bit in the MI serial port Status
register.
2.14.7 AutoNegotiation Enable
The AutoNegotiation algorithm can be enabled (or restarted) by setting
the AutoNegotiation enable bit in the MI serial port Control register or by
asserting the ANEG pin. The AutoNegotiation enable bit and ANEG pin
both have to be high to enable AutoNegotiation. When the
AutoNegotiation algorithm is enabled, the device halts all transmissions
including link pulses for 1200-1500 ms, enters the Link Fail state, and
restarts the negotiation process. When the AutoNegotiation algorithm is
disabled, the selection of 100 Mbps or 10 Mbps mode is determined by
the speed select bit in the MI serial port Control register, and the
selection of Half or Full Duplex is determined by the duplex select bit in
the MI serial port Control register.
2.14.8 AutoNegotiation Reset
The AutoNegotiation algorithm can be initiated at any time by setting the
AutoNegotiation reset bit in the MI serial port Control register.
2.14.9 Link Indication
Receive link detect activity can be monitored through the link detect bit
in the MI serial port Status and Status Output registers or it can also be
programmed to appear on LED status pins by appropriately setting the
programmable LED select bits in the MI serial port Configuration 2
register as shown in Table 4. Whenever the LED Status pins are
Functional Description
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programmed to be a link detect output, these pins are asserted low
whenever the device is in the Link Pass state.
2.14.10 Link Disable
The link integrity function can be disabled by setting the link disable bit
in the MI serial port Configuration 1 register. When the link integrity
function is disabled, the device is forced into the Link Pass state,
configures itself for Half/Full Duplex based on the value of the duplex bit
in the MI serial port Control register, configures itself for 100/ 10 Mbps
operation based on the values of the speed bit in the MI serial port
Control register, and continues to transmit NLP’s or TX idle patterns,
depending on whether the device is in 10 or 100 Mbps mode.
2.15 Jabber
2.15.1 100 Mbps
The jabber function is disabled in the 100 Mbps mode.
2.15.2 10 Mbps
A jabber condition occurs when the transmit packet exceeds a
predetermined length. When jabber is detected, the TP transmit outputs
are forced to the idle state, collision is asserted, and jabber register bits
in the MI serial port Status and Channel Status Output registers are set.
2.16 Receive Polarity Correction
2.16.1 100 Mbps
No polarity detection or correction is needed in 100 Mbps mode.
2.16.2 10 Mbps
The polarity of the signal on the TP receive input is continuously
monitored. If one SOI pulse indicates incorrect polarity on the TP receive
input, the polarity is internally determined to be incorrect, and the reverse
polarity bit is set in the MI serial port Channel Status Output register.
The L84225 will automatically correct for the reverse polarity condition if
the autopolarity feature is not disabled.
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2.17 Full Duplex Mode
2.17.1 100 Mbps
Full Duplex mode allows transmission and reception to occur
simultaneously. When Full Duplex mode is enabled, collision is disabled,
and internal TXEN to CRS loopback is disabled.
The device can be either forced into Half or Full Duplex mode, or the
device can detect either Half or Full Duplex capability from a remote
device and automatically place itself in the correct mode.
Each channel can be forced into the Full or Half Duplex modes by either
setting the duplex bit in the MI serial port Control register or asserting
the DPLX pin for the corresponding channel with AutoNegotiation
disabled.
The device can automatically configure itself for Full or Half Duplex
modes by using the AutoNegotiation algorithm to advertise and detect
Full and Half Duplex capabilities to and from a remote terminal. For
detailed information, refer to Section 2.14, “Link Integrity and
AutoNegotiation,” page 40.
2.17.2 10 Mbps
Full Duplex in 10 Mbps mode is identical to the 100 Mbps mode.
2.17.3 Full Duplex Indication
Full Duplex detect activity can be monitored through the duplex detect bit
in the MI serial port Channel Status Output register.
Full Duplex detect activity also appears on the LED1 pin by default. The
LED outputs can be programmed to indicate four specific sets of events,
by appropriately setting the LED definition bits in the MI serial port Global
Configuration register. Section 2.23, “LED Drivers,” page 48, describes
the programmable LED definition bit settings. Note that Full Duplex
detection appears on the LED1 pin in each of the four sets of events.
The LED1 pin is asserted low when the device is configured for Full
Duplex operation.
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2.18 10/100 MBPS Selection
2.18.1 General
The device can be forced into either the 100 or 10 Mbps mode, or the
device can detect 100 or 10 Mbps capability from a remote device and
automatically place itself in the correct mode.
The device can be forced into either the 100 or 10 Mbps mode by either
setting the speed select bit in the MI serial port Control register or by
setting the SPEED pin with AutoNegotiation disabled. Both the speed
select bit and SPEED pin need to be set to the same speed (10 or 100)
for the device to be properly configured. The speed select bit and SPEED
pin are ignored if AutoNegotiation is enabled.
The device can automatically configure itself for 100 or 10 Mbps mode
by using the AutoNegotiation algorithm to advertise and detect 100 and
10 Mbps capabilities to and from a remote device. Refer to Section 2.14,
“Link Integrity and AutoNegotiation,” page 40, for more details on
AutoNegotiation.
2.18.2 10/100 MBPS Indication
The device speed (100/10 Mbps) can be monitored through the speed
bit in the MI serial port Channel Status Output register.
The device speed can also be programmed to appear on the LED0 pin,
by appropriately setting the LED definition bits in the MI serial port Global
Configuration register. Section 2.23, “LED Drivers,” page 48, describes
the programmable LED definition bit settings. When the LED0 pin is
programmed to be a speed detect output, the pin is asserted low when
the device is configured for 100 Mbps operation.
2.19 Loopback
2.19.1 Internal CRS Loopback
TXEN is internally looped back onto CRS during every transmit packet.
This internal CRS loopback is disabled during collision, in Full Duplex
mode, in Link Fail State, and in RMII mode. In 10 Mbps mode, internal
CRS loopback is also disabled when jabber is detected.
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The internal CRS loopback can be disabled by setting the TXEN to CRS
loopback disable bit in the MI serial port Channel Configuration register.
When this bit is set, TXEN is no longer looped back to CRS.
2.19.2 Diagnostic Loopback
A diagnostic loopback mode can also be selected by setting the loopback
bit in the MI serial port Control register. When diagnostic loopback is
enabled, TXD[3:0] data is looped back onto RXD[3:0], TXEN is looped
back onto CRS, RXDV operates normally, the TP receive and transmit
paths are disabled, the transmit link pulses are halted, and the Half/Full
Duplex modes do not change. Diagnostic loopback mode can not be
enabled when the FBI interface is selected.
2.20 Reset
The L84225 is reset when either:
1. VDD is applied to the device,
2. the reset bit is set in the MI serial port Control register, or
3. the RESET pin is asserted active low.
When the reset is initiated by either (1) or (2), an internal power-on reset
pulse is generated which resets all internal circuits, forces the MI serial
port bits to their default values, and latches in new values for the MI
address. After the power-on reset pulse has finished, the reset bit in the
MI serial port Control register is cleared and the device is ready for
normal operation. The device is guaranteed to be ready for normal
operation 50 ms after the reset was initiated.
When the reset is initiated by (3), the identical procedure takes place as
in (1) and (2), except the device stays in reset until the RESET pin is
deasserted high.
2.21 Powerdown
The L84225 can be powered down by setting the powerdown bit in the
MI serial port Control register. In powerdown mode, the TP outputs are
in high impedance state, all functions are disabled except the MI serial
port, and the power consumption is reduced to a minimum. The device
will be ready for normal operation 50 ms after powerdown is deasserted.
Functional Description
Copyright © 1999-2002 by LSI Logic Corporation. All rights reserved.
47 of 118
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2.22 Clock
The L84225 requires a 25 MHz reference frequency for internal signal
generation in MII mode, and 50 MHz in RMII mode. This reference
frequency must be applied to the CLKIN pin.
2.23 LED Drivers
The LED[3:0] outputs can drive LEDs tied to either VDD or GND. The
LED definitions assume that the LED outputs are active low. If the LED
Anodes are tied to the positive power supply (through limiting resistors),
the LED will indicate the event as shown in Table 4. If the LED Cathodes
are tied to ground and the Anodes to the L84225 Driver output, they will
indicate the respective complementary events.
The LED[3:0] outputs can also drive other digital inputs.
Table 4
LED Function Definition
LEDDEF
LED3
LED2
LED1
LED0
1
0
LINK + ACT
LINK 100
COL
ACT
FDX
FDX
10/100
LINK10
Notes:
When the FX interface is enabled, LED0 becomes FEF. Default = 000
when pin LEDDEF = 0
Bits 16. [13:11] forced to 001 when pin LEDDEF = 1
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Table 5
Symbol
LED Event Definition
Definition
ACT
Activity Occurred, Stretch Pulse to 100 ms
Collision Occurred, Stretch Pulse to 100 ms
100 Mb Link Detected
COL
LINK100
LINK10
LINK
10 Mb Link Detected
100 Mb or 10 Mb Link Detected
LINK+ACT
LED on if Link Detected (10 or 100). LED Blinks if Activity
Determined, Stretch Pulse to 100 ms
FDX
Full Duplex Mode Detected with Link Pass
10/100
10 Mb Mode Enabled (High) or 100 Mb Mode Enabled (Low)
with Link Pass
2.24 Repeater Mode
The L84225 has one predefined repeater mode which can be enabled
by asserting the REPEATER pin. When this mode is enabled, the device
operation is altered as follows:
•
TXEN to CRS loopback is disabled.
2.25 MI Serial Port
2.25.1 Signal Description
The MI serial port has five pins, MDC, MDIO, and PHYAD[4:2]. MDC is
the serial shift clock input. MDIO is a bidirectional data I/O pin.
PHYAD[4:2] are physical address pins.
Pins PHYAD[4:2] set the three most significant bits of the PHY address.
The two least significant bits of the PHY address are set internally to
match the channel number, as shown in Table 6.
Functional Description
Copyright © 1999-2002 by LSI Logic Corporation. All rights reserved.
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Table 6
PHYAD[1:0] Settings
PHYAD1
PHYAD0
Channel 3
Channel 2
Channel 1
Channel 0
1
1
0
0
1
0
1
0
2.25.2 Timing
Figure 9 shows a timing diagram for a MI serial port cycle.
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Figure 9
MI Serial Port Frame Timing Diagram
WRITE Cycle
0
1
1
2
3
4
5
6
7
8
9
10 11 12 13 14 15 16 17 18 19 20 21 22 23 24 25 26 27 28 29 30 31
MDC
MDIO
0
0
1
P4 P3 P2 P1 P0 R4 R3 R2 R1 R0
1
0
D15 D14 D13 D12 D11 D10 D9 D8 D7 D6 D5 D4 D3 D2 D1 D0
ST
OP
PHYAD
REGAD
TA
DATA
WRITE Bits
PHY Clocks In Data on Rising Edges of MDC with t = 10ns Min t = 10ns Min
s
h
READ Cycle
0
1
1
2
0
3
4
5
6
7
8
9
10 11 12 13 14 15 16 17 18 19 20 21 22 23 24 25 26 27 28 29 30 31
MDC
MDIO
0
1
P4 P3 P2 P1 P0 R4 R3 R2 R1 R0
Z 0 D15 D14 D13 D12 D11 D10 D9 D8 D7 D6 D5 D4 D3 D2
D1 D0
ST
OP
PHYAD
REGAD
TA
DATA
WRITE Bits
PHY Clocks In Data on Rising Edges of MDC
with t = 10ns Min t = 10ns Min
READ Bits
PHY Clocks Out Data on Rising Edges of MDC
with t = 20ns Max
s
h
d
The MI serial port is idle when at least 32 continuous 1's are detected
on MDIO and remains idle as long as continuous 1's are detected.
During idle, MDIO is in the high impedance state. When the MI serial port
is in the idle state, a 01 pattern on the MDIO pin initiates a serial shift
cycle. Data on MDIO is then shifted in on the next 14 rising edges of
MDC (MDIO is high impedance). If the register access mode is not
enabled, on the next 16 rising edges of MDC, data is either shifted in or
out on MDIO, depending on whether a write or read cycle was selected
with the bits READ and WRITE. After the 32 MDC cycles have been
completed, one complete register has been read/written, the serial shift
process is halted, data is latched into the device, and MDIO goes into
high impedance state. Another serial shift cycle cannot be initiated until
the idle condition (at least 32 continuous 1's) is detected.
2.25.3 Multiple Register Access
Multiple registers can be accessed on a single MI serial port access
cycle with the multiple register access feature. The multiple register
access feature can be enabled by setting the multiple register access
enable bit in the Global Configuration Register for all channels.
When multiple register access is enabled, all registers can be accessed
on a single MI serial port access cycle by setting the register address to
11111 during the first 16 MDC clock cycles. There is no actual register
residing in register address location 11111.
When the register address is set to 11111, all eleven registers are
accessed for all four channels on the 704 rising edges of MDC (4 x 11
x 16) that occur after the first 16 MDC clock cycles of the MI serial port
access cycle. The registers are accessed in numerical order from 0 to
20 for each channel and from channel 0 to 3. After all 720 MDC clocks
have been completed, all the registers have been read/written, and the
serial shift process is halted, data is latched into the device, and MDIO
goes into high impedance state. Another serial shift cycle cannot be
initiated until the idle condition (at least 32 continuous 1's) is detected.
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2.25.4 Bit Types
Since the serial port is bidirectional, there are many types of bits. The bit
type definitions are summarized in Table 7.
Table 7
Sym.
MI Register Bit Type Definition
Definition
Name
Write Cycle
Read Cycle
W
R
Write
Input
No Operation, Hi Z
Output
Read
No Operation, Hi Z
Input
R/W
Read/Write
Output
R/WSC Read/Write
Self Clearing
Input. Clears Itself After
Operation Completed
Output
R/LL
R/LH
R/LT
Read/Latching
Low
No Operation, Hi Z
No Operation, Hi Z
No Operation, Hi Z
Output. When bit goes low, bit latched.
When bit is read, bit updated.
Read/Latching
High
Output. when bit goes high, bit latched.
When bit is read, bit updated.
Read/Latching on
Transition
Output. When bit transitions, bit latched
and interrupt set. When bit is read, inter-
rupt cleared and bit updated.
Write bits (W) are inputs during a write cycle and are high impedance
during a read cycle. Read bits (R) are outputs during a read cycle and
high impedance during a write cycle. Read/Write bits (R/W) are actually
write bits that can be read out during a read cycle. R/WSC bits are R/W
bits that are self-clearing after a set period of time or after a specific
event has completed. R/LL bits are read bits that latch themselves when
they go low, and they stay latched low until read. After they are read, they
are reset high. R/LH bits are the same as R/LL bits, except that they latch
high. R/LT are read bits that latch themselves whenever they make a
transition or change value, and they stay latched until they are read. After
R/LT bits are read, they are updated to their current value. The R/LT bits
can also be programmed to assert the interrupt function as described in
the Interrupt section.
Functional Description
Copyright © 1999-2002 by LSI Logic Corporation. All rights reserved.
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2.25.5 Frame Structure
The structure of the serial port frame is shown in Table 8 and a timing
diagram is shown in Figure 9. Each serial port access cycle consists of
32 bits (or 720 bits if multiple register access is enabled and
REGAD[4:0]=11111), exclusive of idle. The first 16 bits of the serial port
cycle are always write bits and are used for addressing. The last 16/704
bits are from one/all of the 4 x 11 data registers.
The first 2 bits in Table 8 and Figure 9 are start bits and need to be
written as a 01 for the serial port cycle to continue. The next 2 bits are
read and write bits that determine whether the accessed data register
bits will be read or write. The next 5 bits are device addresses. The 3
most significant bits must match the values on pins PHYAD[4:2] and the
2 least significant bits select one of four channels for access. The next 5
bits are register address select bits, which select one of the eleven
registers for access. The next 2 bits are turnaround bits which are not an
actual register bits but extra time to switch MDIO from write to read if
necessary. The final 16 bits of the MI serial port cycle (or 704 bits if
multiple register access is enabled and REGAD[4:0]=11111) come from
the specific data register designated by the register address bits
REGAD[4:0].
2.25.6 Register Structure
The L84225 has eleven 16 bit registers for each channel. All eleven
registers are available for setting configuration inputs and reading status
outputs. A map of the registers is shown in Table 9. The eleven registers
consist of six registers that are defined by IEEE 802.3 specifications
(Registers 0-5) and five registers that are unique to the L84225
(Registers 16-20).
The structure and bit definition of the Control Register is shown in
Table 10. This register stores various configuration inputs and its bit
definition complies with the IEEE 802.3 specifications.
The structure and bit definition of the Status Register is shown in
Table 11. This register contains device capabilities and status output
information and its bit definition complies with the IEEE 802.3
specifications.
The structure and bit definition of the PHY ID Register 1 and PHY ID
Register 2 is shown in Table 12 and Table 13, respectively. These
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registers contain an identification code unique to the L84225 and their bit
definition complies with the IEEE 802.3 specifications.
The structure and bit definition of the Auto Negotiation Advertisement
and Auto Negotiation Remote End Capability registers is shown in
Table 14 and Table 15, respectively. These registers are used by the Auto
Negotiation algorithm and their bit definition complies with the IEEE
802.3 specifications.
The Global Configuration Register, shown in Table 16, stores various
configuration inputs and is common for all four channels. This register is
reserved for factory use only.
The Channel Configuration Register, shown in Table 17, stores various
configuration inputs unique to each channel. This register is reserved for
factory use only.
The structure and bit definition of the Channel Status Output Register is
shown in Table 18. This register contains output status information from
each channel.
The structure and bit definition of the Global Interrupt Mask Register is
shown in Table 19. This register is common for all four channels. Bit 7 is
the interrupt indication. The 7 least significant bits are the Mask bits for
the R/LT status bits in the Channel Status Output Register.
Register 20 in Table 20 is reserved for factory use only. All bits must be
set to the pre-set default states shown for normal operation.
2.25.7 Invalid Registers
The registers in locations 6-15 and 21-31 are not implemented on the
device and are therefore unused. When an unused register is read, the
value returned can be configured to be either all 0s or all 1s by
appropriately pinstrapping the REGDEF pin.
Functional Description
Copyright © 1999-2002 by LSI Logic Corporation. All rights reserved.
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April, 2002
Figure 10
MDIO Interrupt Pulse
Internal
Interrupt
MDC
MDIO
MDIO High-Z
Pulled High Externally
Interrupt
Pulse
MDIO High-Z
Pulled High Externally
Internal
Interrupt
MDC
B1
B0
MDIO
Last Two Bits
of Read Cycle
Interrupt
Pulse
MDIO High-Z
Pulled High Externally
MDIO High-Z
Pulled High Externally
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3 Register Description
Table 8
MI Serial Port Structure
<Idle>
IDLE
<Start> <Read> <Write> <PHY Addr.> <Reg. Addr.> <Turnaround>
<Data>
D[15:0]
ST[1:0]
READ
WRITE
PHYAD[4:0]
REGAD[4:0]
TA[1:0]
MI Registers - Address and Default Value
REGAD
Name
Default (Hex Code)
00000
00001
00010
00011
00100
00101
10000
10001
10010
10011
10100
Control Register
3000
Status Register
7809
PHY ID 1 Register
0016
PHY ID 2 Register
F840
Auto Negotiation Advertisement Register
01E1
Auto Negotiation Remote Capability Register
0000
Reserved
0008
Reserved
0002
0340/0240/ 0140/0040
007F
Channel Status Output Register
Reserved
Reserved
0000
Symbol
Name
Definition
R/W
IDLE
Idle Pattern
These bits are an idle pattern. Device will not initiate an MI
cycle until it detects at least 32 1's.
W
ST[1:0]
Start Bits
When ST[1:0]=01, a MI serial port access cycle starts.
1 = Read Cycle
W
W
W
W
READ
Read Select
Write Select
WRITE
1 = Write Cycle
PHYAD[4:0]
PhysicalDevice When PHYAD[4:2] bits match the PHYAD[4:2] pins, the MI
Address
serial port is selected for operation. PHYAD[1:0] is used for
channel selection:
PHYAD [1:0]=11 For Channel 3
PHYAD [1:0]=10 For Channel 2
PHYAD [1:0]=01 For Channel 1
PHYAD [1:0]=00 For Channel 0
REGAD4[4:0] Register
Address
If REGAD[4:0]=00000-11100, these bits determine the
specific register from which D[15:0] is read/written. If mul-
tiple register access is enabled and REGAD[4:0]=11111,
all registers are read/written in a single cycle.
W
Register Description
Copyright © 1999-2002 by LSI Logic Corporation. All rights reserved.
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April, 2002
Symbol
Name
Definition
R/W
TA[1:0]
Turnaround
Time
These bits provide some turnaround time for MDIO
When READ=1, TA[1:0]=Z0
R/W
When WRITE=1, TA[1:0]=ZZ
D[15:0]+
Data
These 16 bits contain data to/from one of the eleven regis- R or
ters selected by register address bits REGAD[4:0].
W
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Table 9
MI Serial Port Register Map
x.15
RST
R/WSC
0
x.14
LPBK
R/W
0
x.13
x.12
x.11
PDN
R/W
0
x.10
x.9
x.8
DPLX
R/W
0
x.7
COLTST
R/WSC
0
x.6
0
x.5
0
x.4
0
x.3
0
x.2
0
x.1
0
x.0
SPEED ANEG_EN
MII_DIS ANEG_RST
0
0 Control
R/W
1
R/W
1
R/W
0
R/WSC
R
0
R
0
R
0
R
0
R
R
R
0
0
0
0
0
CAP_T4 CAP_TXF CAP_TXH CAP_TF CAP_TH
0
0
0
CAP_
SUPR
ANEG_ REM_FLT CAP_
ACK
LINK
JAB
EXREG
1 Status
ANEG
R
R
R
R
R
R
R
R
R
R
R
R/LH
R
R/LL
R/LH
R
0
1
1
1
1
0
0
0
0
0
0
0
1
0
0
1
OUI3
OUI4
OUI5
OUI6
OUI7
OUI8
OUI9
OUI10
OUI11
OUI12
OUI13
OUI14
OUI15
OUI16
OUI17
OUI18
2 PHY ID #1
3 PHY ID #2
R
R
R
R
R
R
R
R
R
R
R
R
R
0
R
1
R
1
R
0
0
OUI19
R
0
OUI20
R
0
OUI21
R
0
OUI22
R
0
OUI23
R
0
OUI24
R
0
0
0
0
0
1
PART5
PART4
PART3
PART2
PART1
PART0
REV3
R
REV2
R
REV1
R
REV0
R
R
0
R
0
R
0
R
1
R
0
R
0
1
1
1
1
1
0
--
--
--
--
NP
R/W
0
ACK
R
RF
R/W
0
0
R/W
0
0
R/W
0
PAUSE
R/W
0
T4
R/W
0
TX_FDX TX_HDX 10_FDX
0
R/W
1
0
R/W
0
0
R/W
0
0
R/W
0
0
R/W
0
CSMA
R/W
1
4 AutoNegot.
Advertisement
R/W
1
R/W
1
R/W
1
0
NP
R
ACK
R
RF
R
0
0
R
0
0
R
0
PAUSE
T4
R
0
TX_FDX TX_HDX 10_FDX
0
R
0
0
R
0
0
R
0
0
R
0
0
R
0
CSMA
5. AutoNegot.
Remote
R
0
0
R
0
0
R
0
0
R
0
1
R
0
0
Capability
0
0
0
0
0
0
0
0
0
0
1
0
0
16 Reserved
R/W
0
R/W
0
R/W
0
R/W
0
R/W
0
R/W
0
R/W
R/W
R/W
0
R/W
1
R/W
0
R/W
0
R/W
R/W
0
R/W
0
R/W
0
0
0
0
0
1
0
0
0
0
0
0
0
0
0
0
0
0
1
0
17 Reserved
R/W
0
R/W
0
R/W
0
R/W
0
R/W
0
R/W
0
R/W
0
R/W
0
R/W
0
R/W
0
R/W
0
R/W
0
R/W
0
R/W
0
R/W
1
R/W
0
RPOL DSYN_TO
0
0
0
0
CHAD1
CHAD0
0
LINK_
FAIL
SPD_
DET
DPLX_
DET
CWRD
SSD
ESD
JAB
18 Channel
Status
Output
R
0
R
0
R
0
R
0
R
0
R
0
R
R
R
0
R/LT
1
R/LT
0
R/LT
0
R/LT
0
R/LT
0
R/LT
0
R/LT
0
11/10/01/00 11/10/01/00
0
R/W
0
0
R/W
0
0
R/W
0
0
R/W
0
0
R/W
0
0
R/W
0
0
R/W
0
0
R/W
0
0
R/W
0
1
R/W
1
1
R/W
1
1
R/W
1
1
R/W
1
1
R/W
1
1
R/W
1
1
R/W
1
19 Reserved
20 Reserved
0
0
0
0
0
0
0
0
0
0
0
0
0
0
0
0
R/W
0
R/W
0
R/W
0
R/W
0
R/W
0
R/W
0
R/W
0
R/W
0
R/W
0
R/W
0
R/W
0
R/W
0
R/W
0
R/W
0
R/W
0
R/W
0
Table 10
Register 0 - Control Register Definition
0.15
RST
0.14
LPBK
R/W
0.13
SPEED
R/W
0.12
ANEG_EN
R/W
0.11
PDN
R/W
0.10
MII_DIS
R/W
0.9
0.8
DPLX
R/W
ANEG_RST
R/WSC
R/WSC
0.7
0.6
0
0.5
0
0.4
0
0.3
0
0.2
0
0.1
0
0.0
0
COLTST
R/WSC
R
R
R
R
R
R
R
Bit
Symbol
Name
Definition
R/W Def.
0.15
RST
Reset
1 = Reset, Bit Self Clearing after Reset Complete R/W
0
0
1
0 = Normal SC
SC
0.14
0.13
LPBK
SPEED
Loopback
Enable
1 = Loopback Mode Enabled
0 = Normal
R/W
Speed
Select
1 = 100 Mbps Selected (100BaseTX)
0 = 10 Mbps Selected (10BaseT)
Note: Can be overridden with SPEED pin
R/W
R/W
0.12
ANEG_EN
AutoNegoti- 1 = AutoNegotiation Enabled
ation Enable 0 = AutoNegotiation Disabled
1
Note: Can be overridden with ANEG pin
0.11
0.10
0.9
PDN
Powerdown 1 = Powerdown
Enable 0 = Normal
R/W
R/W
0
1
0
MII_DIS
MII Interface 1 = MII Interface Disabled
Disable 0 = Normal
ANEG_RST AutoNegoti- 1 = Restart AutoNegotiation Process, Bit Self
ation Reset Clearing After Reset Complete
0 = Normal
R/W
SC
0.8
0.7
DPLX
Duplex
Mode Select 0 = Half Duplex
Note: Can be overridden with DPLX pin
1 = Full Duplex
R/W
0
COLTST
Collision
1 = Collision Test Enabled
R/W
R/W
0
0
Test Enable 0 = Normal
0.6 thru
0.0
Reserved
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Copyright © 1999-2002 by LSI Logic Corporation. All rights reserved.
Table 11
Register 1 - Status Register Definition
1.15
CAP_T4
R
1.14
CAP_TXF
R
1.13
CAP_TXH
R
1.12
CAP_TF
R
1.11
CAP_TH
R
1.10
0
1.9
0
1.8
0
R
R
R
1.7
0
1.6
1.5
1.4
1.3
1.2
1.1
JAB
R/LH
1.0
EXREG
R
CAP_SUPR ANEG_ACK REM_FLT CAP_ANEG
LINK
R/LL
R
R
R
R/LH
R
Bit
Symbol
Name
Definition
R/W Def.
1.15
CAP_T4
100Base-T4
Capable
0 = Not Capable of 100Base-T4 Operation
R
R
R
R
R
R
0
1
1
1
1
0
1.14
1.13
1.12
1.11
CAP_TXF
100Base-TX Full 1 = Capable Of 100Base-TX Full Duplex
Duplex Capable
CAP_TXH 100Base-TX Half 1 = Capable Of 100Base-TX Half Duplex
Duplex Capable
CAP_TF
10Base-T Full
Duplex Capable
1 = Capable Of 10Base-T Full Duplex
1 = Capable Of 10Base-T Half Duplex
Reserved
CAP_TH
10Base-T Half
Duplex Capable
1.10
thru
1.7
1.6
1.5
1.4
CAP_SUPR MI Preamble
Suppression
0 = Not Capable of Accepting MI Frames
with MI Preamble Suppressed
R
R
0
0
0
Capable
ANEG_ACK AutoNegotiation
1 = AutoNegotiation Acknowledgement Pro-
Acknowledgment cess Complete
0 = AutoNegotiation Not Complete
REM_FLT
Remote Fault
Detect
1 = Remote Fault Detected. This bit is set R/LH
when Remote Fault Bit 5.13 is set.
0 = No Remote Fault
1.3
1.2
CAP_ANEG AutoNegotiation
Capable
1 = Capable of AutoNegotiation
R
1
0
LINK
Link Status
1 = Link Detected (Same as Bit 18.6
Inverted)
R/LL
0 = Link Not Detected
Register Description
Copyright © 1999-2002 by LSI Logic Corporation. All rights reserved.
61 of 118
April, 2002
Bit
Symbol
Name
Definition
R/W Def.
1.1
JAB
Jabber Detect
1 = Jabber Detect
0 = Normal
R/LH
R
0
1
1.0
EXREG
Extended Regis- 1 = Extended Registers Exist
ter Capable
Note: 1.15 Bit is Shifted First
Table 12
Register 2 - PHY ID Register 1 Definition
2.15
OUI3
R
2.14
OUI4
R
2.13
OUI5
R
2.12
OUI6
R
2.11
OUI7
R
2.10
OUI8
R
2.9
OUI9
R
2.8
OUI10
R
2.7
OUI11
R
2.6
OUI12
R
2.5
OUI13
R
2.4
OUI14
R
2.3
OUI15
R
2.2
OUI16
R
2.1
OUI17
R
2.0
OUI18
R
Bit
Symbol Name
Definition
OUI = 00-A0-7D
R/W Def.
2.15
2.14
2.13
2.12
2.11
2.10
2.9
2.8
2.7
2.6
2.5
OUI3
OUI4
CompanyID, Bits 3-18
R
0
0
0
0
0
0
0
0
0
0
0
1
0
1
1
0
OUI5
OUI6
OUI7
OUI8
OUI9
OUI10
OUI11
OUI12
OUI13
OUI14
OUI15
OUI16
OUI17
OUI18
2.4
2.3
2.2
2.1
2.0
Note: 2.15 Bit is Shifted First
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L84225 Quad 100BaseTX/FX/10BaseT Phys. Layer Device - Technical Manual
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Table 13
Register 3 - PHY ID Register 2 Definition
3.15
OUI19
R
3.14
OUI20
R
3.13
OUI21
R
3.12
OUI22
R
3.11
OUI23
R
3.10
OUI24
R
3.9
PART5
R
3.8
PART4
R
3.7
PART3
R
3.6
PART2
R
3.5
PART1
R
3.4
PART0
R
3.3
REV3
R
3.2
REV2
R
3.1
REV1
R
3.0
REV0
R
Bit
Symbol Name
Definition
OUI = 00-A0-7D
R/W
Def.
3.15
3.14
3.13
3.12
3.11
3.10
OUI19
OUI20
OUI21
OUI22
OUI23
OUI24
Company ID, Bits 3-18
R
1
1
1
1
1
0
3.9
3.8
3.7
3.6
3.5
3.4
PART5
PART4
PART3
PART2
PART1
PART0
Manufacturer's Part Number
04
R
R
0
0
0
1
0
0
3.3
3.2
3.1
3.0
REV3
REV2
REV1
REV0
Manufacturer's Revision Number
Note: 3.15 Bit is Shifted First
–
–
–
–
Register Description
Copyright © 1999-2002 by LSI Logic Corporation. All rights reserved.
63 of 118
April, 2002
Table 14
Register 4 - AutoNegotiation Advertisement Register Definition
4.15
NP
4.14
ACK
R
4.13
RF
4.12
0
4.11
0
4.10
PAUSE
R/W
4.9
T4
4.8
TX_FDX
R/W
R/W
R/W
R/W
R/W
R/W
4.7
TX_HDX
R/W
4.6
10_FDX
R/W
4.5
0
4.4
0
4.3
0
4.2
0
4.1
0
4.0
CSMA
R/W
R/W
R/W
R/W
R/W
R/W
Bit
Symbol Name
Definition
R/W Def.
4.15
4.14
NP
Next Page Enable 0 = No Next Page
R/W
R
0
0
ACK
Acknowledge
1 = AutoNegotiation Word Recognized
0 = Not Recognized
4.13
RF
Remote Fault
1 = AutoNegotiation Remote Fault Detected R/W
0 = No Remote Fault
0
0
0
4.12 thru
4.11
Reserved
R/W
4.10
PAUSE PAUSE Frame
Capable
1 = Capable of Transmitting and Receiving
Pause Frames
R/W
0 = Not Capable
4.9
4.8
4.7
4.6
4.5
T4
100Base-T4
Capable
1 = Capable Of 100Base-T4
0 = Not Capable
R/W
R/W
R/W
R/W
R/W
R/W
R/W
0
1
1
1
1
0
1
TX_FDX 100Base-TX Full
Duplex Capable
1 = Capable of 100Base-TX Full Duplex
0 = Not Capable
TX_HDX 100Base-TX Half
Duplex Capable
1 = Capable Of 100Base-TX Half Duplex
0 = Not Capable
10_FDX 10Base-TX Full
Duplex Capable
1 = Capable Of 10Base-TX Full Duplex
0 = Not Capable
10_HDX 10Base-TX Half
Duplex Capable
1 = Capable Of 10Base-TX Half Duplex
0 = Not Capable
4.4 thru
4.1
Reserved
4.0
CSMA CSMA 802.3
Capable
1 = Capable of 802.3 CSMA Operation
0 = Not Capable
Note: 4.15 Bit is Shifted First
64 of 118
April, 2002
L84225 Quad 100BaseTX/FX/10BaseT Phys. Layer Device - Technical Manual
Copyright © 1999-2002 by LSI Logic Corporation. All rights reserved.
Table 15
Register 5 - AutoNegotiation Remote Capability Defintion
5.15
NP
R
5.14
ACK
R
5.13
RF
R
5.12
0
5.11
0
5.10
PAUSE
R
5.9
T4
R
5.8
TX_FDX
R
R
R
5.7
TX_HDX
R
5.6
10_FDX
R
5.5
0
5.4
0
5.3
0
5.2
0
5.1
0
5.0
CSMA
R
R
R
R
R
R
Bit
Symbol Name
Definition
R/W Def.
5.15
NP
ACK
RF
Next Page Enable 1 = Next Page Exists
0 = No Next Page
R
R
R
R
R
0
0
0
0
0
5.14
5.13
Acknowledge
1 = Received AutoNeg. Word Recognized
0 = Not Recognized
Remote Fault
Enable
1 = AutoNegotiation Remote Fault Detected
0 = No Remote Fault
5.12 thru
5.11
Reserved
5.10
PAUSE PAUSE Frame
Capable
1 = Capable of Transmitting and Receiving
Pause Frames
0 = Not Capable
5.9
5.8
5.7
5.6
5.5
T4
100Base-T4
Capable
1 = Capable Of 100Base-T4
0 = Not Capable
R
R
R
R
R
R
R
0
1
0
0
0
0
0
TX_FDX 100Base-TX Full
Duplex Capable
1 = Capable of 100BaseTx Full Duplex
0 = Not Capable
TX_HDX 100Base-TX Half
Duplex Capable
1 = Capable Of 100BaseTx Half Duplex
0 = Not Capable
10_FDX 10Base-TX Full
Duplex Capable
1 = Capable Of 10BaseTx Full Duplex
0 = Not Capable
10_HDX 10Base-TX Half
Duplex Capable
1 = Capable Of 10BaseTx Half Duplex
0 = Not Capable
5.4 thru
5.1
Reserved
5.0
CSMA CSMA 802.3
Capable
1 = Capable of 802.3 CSMA Operation
0 = Not Capable
Note: 5.15 Bit is Shifted First
Register Description
Copyright © 1999-2002 by LSI Logic Corporation. All rights reserved.
65 of 118
April, 2002
Table 16
Register 16 - Reserved
16.15
0
16.14
0
16.13
0
16.12
0
16.11
0
16.10
0
16.9
0
16.8
0
R/W
R/W
R/W
R/W
R/W
R/W
R/W
R/W
16.7
0
16.6
1
16.5
0
16.4
0
16.3
1
16.2
0
16.1
0
16.0
0
R/W
R/W
R/W
R/W
R/W
R/W
R/W
R/W
Bit
Symbol Name Definition
R/W
Def.
16.15 thru
16.0
—
—
Reserved for factory use. Must be written with
default values specified above for normal operation
—
—
66 of 118
April, 2002
L84225 Quad 100BaseTX/FX/10BaseT Phys. Layer Device - Technical Manual
Copyright © 1999-2002 by LSI Logic Corporation. All rights reserved.
Table 17
Register 17 - Reserved
17.15
0
17.14
0
17.13
0
17.12
0
17.11
0
17.10
0
17.9
0
17.8
0
R/W
R/W
R/W
R/W
R/W
R/W
R/W
R/W
17.7
0
17.6
0
17.5
0
17.4
0
17.3
0
17.2
0
17.1
1
17.0
0
R/W
R/W
R/W
R/W
R/W
R/W
R/W
R/W
Bit
Symbol Name Definition
R/W
Def.
17.15 thru
17.0
—
—
Reserved for factory use. Must be written with
default values specified above for normal operation
—
—
Register Description
Copyright © 1999-2002 by LSI Logic Corporation. All rights reserved.
67 of 118
April, 2002
Table 18
Register 18 - Channel Status Output Register Definition
18.15
RPOL
R
18.14
DSYN_TO
R
18.13
18.12
18.11
R
18.10
R
18.9
CHAD1
R
18.8
CHAD0
R
R
R
18.7
R
18.6
18.5
18.4
18.3
CWRD
R/LT
18.2
SSD
R/LT
18.1
ESD
R/LT
18.0
JAB
R/LT
LINK_FAIL SPD_DET DPLX_DET
R/LT
R/LT
R/LT
Bit
Symbol
Name
Definition
R/W
Default
18.15
RPOL
Reversed
Polarity Detect
1 = Reversed Polarity Detect
0 = Normal
R
R
0
18.14
DSYN_TO
Loss of Syn-
chronization
Detect
1 = Descrambler Has Lost
Synchronization
0 = Normal
0
0
18.13
thru
18.10
Reserved
R
R
18.9
18.8
CHAD1
CHAD0
Channel
Address
11 = Accessing Channel 3
10 = Accessing Channel 2
01 = Accessing Channel 1
00 = Accessing Channel 0
11/10/
01/00
18.7
18.6
Reserved
R
0
1
LINK_FAIL
SPD_DET
DPLX_DET
CWRD
Link Fail Detect 1 = Link Not Detected
0 = Normal
R/LT
18.5
18.4
18.3
100/10 Speed
Detect
1 = Device in 100BaseTx Mode
0 = Device in 10 BaseT Mode
R/LT
R/LT
R/LT
0
0
0
Duplex Detect
1 = Device in Full Duplex Mode
0 = Device in Half Duplex Mode
Codeword
Error
1 = Invalid 4B5B Code Detected On
Receive Data
0 = Normal
18.2
SSD
Start of Stream
Error
1 = No Start of Stream Delimiter
Detected On Receive Data
0 = Normal
R/LT
0
68 of 118
April, 2002
L84225 Quad 100BaseTX/FX/10BaseT Phys. Layer Device - Technical Manual
Copyright © 1999-2002 by LSI Logic Corporation. All rights reserved.
Bit
Symbol
Name
Definition
R/W
Default
18.1
ESD
End of Stream
Error
1 = No End of Stream Delimiter
Detected On Receive Data
0 = Normal
R/LT
0
18.0
JAB
Jabber Detect
1 = Jabber Detected
0 = Normal
R/LT
0
Note: 18.15 Bit Is Shifted First
Register 19 - Reserved
Table 19
19.15
0
19.14
0
19.13
0
19.12
0
19.11
0
19.10
0
19.9
19.8
0
0
R/W
R/W
R/W
R/W
R/W
R/W
R/W
R/W
19.7
0
19.6
1
19.5
1
19.4
1
19.3
1
19.2
1
19.1
1
19.0
1
R/W
R/W
R/W
R/W
R/W
R/W
R/W
R/W
Bit
Symbol Name Definition
R/W
Def.
19.15 thru
19.0
—
—
Reserved for factory use. Must be written with
default values specified above for normal operation
—
—
Register Description
Copyright © 1999-2002 by LSI Logic Corporation. All rights reserved.
69 of 118
April, 2002
Table 20
Register 20 - Reserved
20.15
0
20.14
0
20.13
0
20.12
0
20.11
0
20.10
0
20.9
0
20.8
0
R/W
R/W
R/W
R/W
R/W
R/W
R/W
R/W
20.7
0
20.6
0
20.5
0
20.4
0
20.3
0
20.2
0
20.1
0
20.0
0
R/W
R/W
R/W
R/W
R/W
R/W
R/W
R/W
Bit
Symbol Name Definition
R/W
Def.
20.15 thru
20.0
—
—
Reserved for factory use. Must be written with
default values specified above for normal operation
—
—
Note: 20.15 Bit Is Shifted First
4 Application Information
4.1 Example Schematics
A typical example of the L84225 used for a switching hub application in
twisted pair mode is shown in Figure 11; an example of the L84225 used
in fiber mode is shown in Figure 12.
4.2 TP Interface
4.2.1 Transmit Interface
The interface between the TP outputs on TPOP/N and the twisted pair
cable is typically transformer coupled and terminated with the two
resistors as shown in Figure 11.
The transformer for the transmitter is recommended to have a winding
ratio of 1:1 with the center tap of the primary winding tied to VDD, as
shown in Figure 11. The specifications for such a transformer are shown
in Table 21. Sources for quad transformers compatible with the L84225
are listed in Table 22. Note that both “Stacked” and “Non-Stacked” pinout
types are listed. The Stacked and Non-Stacked designation refers to the
70 of 118
April, 2002
L84225 Quad 100BaseTX/FX/10BaseT Phys. Layer Device - Technical Manual
Copyright © 1999-2002 by LSI Logic Corporation. All rights reserved.
type of RJ-45 connector used on the secondary side (line side) of the
transformer. The pinout of these types differ slightly so that traces to the
magnetics may be kept as short and direct as possible.
The "non-stacked" RJ-45 (also referred to as harmonica) is a traditional
horizontally oriented connector consisting of four RJ-45 jacks in a single
in-line assembly.
The newer "stacked" connector consists of a two-over-two configuration
so that four RJ-45 jacks are located in the footprint area of two side-by-
side connectors. This is a significant improvement for higher density
multi-port applications and smaller system form-factors.
The L84225 pin-out has been optimized for connection to transformers
and connectors designed for the higher density stacked configuration.
The Quad Transceiver also operates with non-stacked connectors using
either transformers that map the pin-out to the non-stacked configuration,
or using trace "crossovers" on the PCB layout.
The transformers listed with "non-stacked" pinouts use crossover
connections inside the part to map the stacked pinout of the L84225 to
non-stacked RJ-45 connectors. Crossovers internal to the transformer
are not made in a controlled impedance environment, so this can impact,
somewhat, the cross-talk performance of the system.
For best cross-talk and system performance, it is suggested that stacked
connector and transformer configurations be used. Alternately, non-
stacked connectors may be used with stacked transformer types and the
crossover wiring can be put on the pc board using a ground plane to
reduce impedance mismatch.
The transmit output needs to be terminated with two external termination
resistors in order to meet the output impedance and return loss
requirements of IEEE 802.3. It is recommended that these two external
resistors be connected from VDD to each of the TPOP/N outputs, and
their value should be chosen to provide the correct termination
impedance when looking back through the transformer from the twisted
pair cable, as shown in Figure 11. The value of these two external
termination resistors depends on the type of cable driven by the device.
Refer to the Cable Selection Section for more details on choosing the
value of these resistors.
Application Information
Copyright © 1999-2002 by LSI Logic Corporation. All rights reserved.
71 of 118
April, 2002
To minimize common mode output noise and to aid in meeting radiated
emissions requirements, it may be necessary to add a common mode
choke on the transmit outputs as well as add common mode bundle
termination. The transformers listed in Table 22 all contain common
mode chokes on both the transmit and receive sides, as shown in
Figure 11. Common mode bundle termination is achieved by tying the
unused pairs in the RJ45 to chassis ground through 75 ohm resistors
and a 0.01 uF capacitor, as shown in Figure 11.
To minimize noise pickup into the transmit path in a system or on a PCB,
the loading on TPOP/N should be minimized and both outputs should
always be loaded equally.
Table 21
TP Transformer Specification
Specification
Parameter
Transmit
Receive
Turns Ratio
1:1 CT
350
0.2
1:1
350
0.2
15
Inductance, (uH Min)
Leakage Inductance, (uH)
Capacitance (pF Max)
DC Resistance (Ohms Max)
15
0.4
0.4
72 of 118
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L84225 Quad 100BaseTX/FX/10BaseT Phys. Layer Device - Technical Manual
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Figure 11
Typical Switching Hub Port Schematic Using the L84225 in Twisted Pair
Mode
19
50 50
TXCLK_3 VDD
TXD3_3
TXD2_3
TXD1_3
TXD0_3
TXEN_3
TXER_3
COL_3
RXCLK_3
RXD3_3
RXD2_3
RXD1_3
RXD0_3
CRS_3
1%
1%
1:1
1:1
L84302
TPOP_3
TPON_3
16 MII
or
6 RMII
1
2
RJ45
QUAD
4
5
7
8
3
6
Switch
Fabric
100/10 MB
Ethernet
Controller
25
25
TPIP_3
TPIN_3
0.01
RXDV_3
RXER_3
25
25
75
75
L84225
TXCLK_0
TXD3_0
TXD2_0
TXD1_0
TXD0_0
TXEN_0
TXER_0
COL_0
RXCLK_0
RXD3_0
RXD2_0
RXD1_0
RXD0_0
CRS_0
0.01
16 MII
or
6 RMII
50 50
1%
1%
1:1
1:1
TPOP_0
TPON_0
1
2
2
RXDV_0
RXER_0
RJ45
4
5
7
8
3
6
MDIO, MDC
25
25
TPIP_0
TPIN_0
0.01
16
LED[3:0]_[3:0]
25
25
REGDEF
DPLX[3:0]
SPEED[3:0]
ANEG
REPEATER
RMII_EN
75
75
REXT
10 K
0.01
PINSTRAP
AD_REV
LEDDEF
4
SD_[3:0]/
FXEN_[3:0]
System Reset
System Clock
RESET
CLKIN
SD_THR
GND
18
Application Information
Copyright © 1999-2002 by LSI Logic Corporation. All rights reserved.
73 of 118
April, 2002
Figure 12
Typical Switching Hub Port Schematic Using the L84225 in FX Mode with
3.3 V Transceivers
19
GEN
70
GEN
70
VDD
TXCLK_3
TXD3_3
TXD2_3
TXD1_3
TXD0_3
TXEN_3
TXER_3
COL_3
RXCLK_3
RXD3_3
RXD2_3
RXD1_3
RXD0_3
CRS_3
VDD
TD
FXOP_3
FXON_3
TDB
GEN
127
GEN
127
GEN
173
GEN
173
16
RD
RDB
FXIP_3
FXIN_3
3.3 V
Optic
Transceiver
QUAD
Switch
Fabric
GEN
83
GEN
83
RXDV_3
RXER_3
100/10 MB
Ethernet
Controller
GEN
127
L84225
SD
GEN
83
TXCLK_0
TXD3_0
TXD2_0
TXD1_0
TXD0_0
TXEN_0
TXER_0
COL_0
16
RXCLK_0
RXD3_0
RXD2_0
RXD1_0
RXD0_0
CRS_0
GEN
GEN
70
70
VDD
TD
FXOP_0
FXON_0
TDB
RXDV_0
RXER_0
GEN
127
GEN
127
GEN
173
GEN
173
2
RD
MDIO/MDC
RDB
FXIP_0
FXIN_0
3.3 V
Optic
Transceiver
16
LED[3:0]_[3:0]
GEN
83
GEN
83
GEN
REGDEF
DPLX[3:0]
SPEED[3:0]
ANEG
REPEATER
RMII_EN
127
SD
SD_0
GEN
83
PINSTRAP
AD_REV
LEDDEF
REXT
10 K
SD_THR
System Reset
System Clock
RESET
CLKIN
GND
18
74 of 118
April, 2002
L84225 Quad 100BaseTX/FX/10BaseT Phys. Layer Device - Technical Manual
Copyright © 1999-2002 by LSI Logic Corporation. All rights reserved.
Table 22
Vendor
TP Transformer Sources
Part Number
Pin Out Type
Pulse
bel
H1062
Stacked
S558-5999B47
6931-30
Stacked
nano pulse
Valor
Stacked
ST6179
Stacked
Halo
TG110-S453NX
H1053
Stacked
Pulse
bel
Non-Stacked
Non-Stacked
Non-Stacked
Non-Stacked
Non-Stacked
S558-5999-J5
6949-30
nano pulse
Valor
ST6403P
Halo
TG110-S456NX
4.2.2 Receive Interface
Receive data is typically transformer coupled into the receive inputs on
TPIP/N and terminated with an external resistor as shown in Figure 11.
The transformer for the receiver is recommended to have a winding
ration of 1:1, as shown in Figure 11. The specifications for such a
transformer are shown in Table 21. Sources for the transformer are listed
in Table 22.
The receive input needs to be terminated with the correct termination
impedance to meet the input impedance and return loss requirements of
IEEE 802.3. In addition, the receive TP inputs need to be attenuated. It
is recommended that both the termination and attenuation be
accomplished by placing four external resistors in series across the
TPIP/N inputs as shown in Figure 11. The resistors should be
25%/25%/25%/25% of the total series resistance, and the total series
resistance should be equal to the characteristic impedance of the cable
(100 ohms for UTP, 150 Ohms for STP). For 100 Ohm twisted pair, the
resistor string values should be 25 Ohms each (1%). It is also
recommended that a 0.1uF capacitor be placed between the center of
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the series resistor string and Vcc in order to provide an AC ground for
attenuating common mode signal at the input. This capacitor is also
shown in Figure 11.
To minimize common mode input noise and to aid in meeting
susceptibility requirements, it may be necessary to add a common mode
choke on the receive input as well as add common mode bundle
termination. The transformers listed in Table 22 contain common mode
chokes on both the transmit and receive sides, as shown in Figure 11.
Common mode bundle termination is achieved by tying the receive
secondary center tap and the unused pairs in the RJ45 to chassis ground
through 75 ohm resistors and a 0.01 uF capacitor, as shown in Figure 11.
In order to minimize noise pickup into the receive path in a system or on
a PCB, the loading on TPIP/N should be minimized and both inputs
should be loaded equally.
4.3 TP Transmit Output Current Set
The TPOP/N output current level is set by an external resistor tied
between REXT and GND. This output current is determined by the
following equation where R is the value of REXT:
I
= (10K/R) I
ref
out
Where I
= 40 mA (100 Mbps, UTP)
ref
= 32.6 mA (100 Mbps, STP)
= 100 mA (10 Mbps, UTP)
= 81.6 mA (10 Mbps, STP)
For 100 Ohm UTP, REXT should be typically set to 10K ohms and REXT
should be a 1% resistor in order to meet IEEE 802.3 specified levels.
Once REXT is set for the 100 Mbps and UTP modes as shown by the
equation above, Iref is then automatically changed inside the device
when the 10 Mbps mode or UTP120/STP150 modes are selected as
described in Section 5.3, “Twisted Pair Characteristics, Transmit,”
page 89.
Keep resistor REXT as close to pins REXT and GND as possible in order
to reduce noise pickup into the transmitter.
Since the TP output is a current source, capacitive and inductive loading
can reduce the output voltage level from the ideal. Thus, in an actual
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application, it might be necessary to adjust the value of the output current
to compensate for external loading. The TP output level can be adjusted
by changing the value of the external resistor tied to RXT.
4.4 Transmitter Droop
The IEEE 802.3 specification has a transmitter output droop requirement
for 100BaseTX. Since the L84225 TP output is a current source, it has
no perceptible droop by itself. However, the open circuit inductance of the
transformer added to the device transmitter output as shown in Figure 11
will cause droop to appear at the transmit interface to the TP wire. If the
transformer connected to the L84225 outputs meets the requirements in
Table 21, the transmit interface to the TP cable will meet the IEEE 802.3
droop requirements.
4.5 Fiber Interface
4.5.1 General
The L84225 uses a PECL-type driver/receiver to achieve a throughput of
100 Mbps across a differential fiber interface. The interface comprises
four signals: FXOP/ FXON (output) and FXIP/FXIN (input).
Some Fiber transceivers modules that will work with the L84225 are
shown in Table 23. The Siemens Fiber Transceiver V23809-C8-C10
operates at 3.3V for use with the L84225. 5V Fiber modules such as the
HP HFBR-5103 will also operate with the proper termination network
described later.
Table 23
Vendor
Fiber Transceiver Modules
3.3V
5V
Siemens1
HP
V23809-C8-C10
Available Soon
Contact Supplier
V23809-C8-C10
HFBR-5103
269040-1
Amp
1. Siemens part operates at both 3.3V and 5V supply values.
The L84225 fiber interface is enabled for each channel independently if
a valid PECL Fiber signal is tied to the SD_[3:0]/FXEN_[3:0] pins; the
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fiber interface is disabled (and the TP interface enabled) by connecting
the SD_[3:0]/FXEN_[3:0] pins to GND for that channel.
AutoNegotiation and the scrambler/descrambler are disabled when the
fiber interface is enabled.
The voltage applied to the SD_THR pin sets the input reference level of
the fiber interface for the single ended Signal Detect inputs only. If a 3.3
V fiber transceiver is used with the L84225, this pin should be tied to
GND. If a 5 V fiber transceiver is used, this pin needs to be tied to
VCC(3.3V)-1.3 V (about 2V), but referenced to the 5V supply of the fiber
transceiver. An easy way to do this is with a 15K:10K voltage divider from
the 5 V supply to ground, with the center point of the divider connected
to SD_THR, as shown in Figure 14.
4.5.2 Operation with 3.3V Fiber Transceivers
Termination on the differential outputs of the fiber transceiver module
must be observed for proper impedance matching, which is normally the
equivalent of 50 Ohms single ended. The terminating resistor values are
shown in Figure 13 for FXOP/FXON (outputs), FXIP/ FXIN (inputs) and
SD_[3:0]/FXEN_[3:0] (inputs) for use with 3.3V fiber modules. The
calculated termination resistors on FXOP/FXON are a pull-up of 69.8
Ohms to 3.3V and a pulldown of 174 Ohms to ground.
The termination network at the fiber inputs (FXIP/FXIN and
SD_[3:0]/FXEN_[3:0]) of the L84225 is specified by the fiber module
manufacturer and will normally be a pull-up of 127 Ohms to 3.3V and a
pulldown of 82.5 Ohms to GND, as shown in Figure 13. Note that the
Input and Output termination resistor values are different since the output
driver of the Fiber module and the L84225 have a different structure. The
interface network for 3.3V fiber transceiver modules is shown in
Figure 13.
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Figure 13
FX Interface to 3.3V Fiber Modules
3.3V
3.3V
69.8
VDD = 3.3V
VDD = 3.3V
TD
TD-
FXOP
FXON
3.3 V
Fiber
127
174
L84220
Transceiver
10/100 TX/FX
Transceiver
RD
RD-
SD
FXIP
127
FXIN
82.5
SD/FXEN
SD_THR
82.5
4.5.3 Operation with 5V Fiber Transceivers
It is also possible to use the L84225 with 5V fiber modules by changing
the resistive termination network slightly.
Since the L84225 FXOP/FXON Outputs are 5V tolerant, the output
termination resistors should be a pull-up of 61.9 Ohms to the 5V supply,
and a pulldown of 261 Ohms to GND, as shown in Figure 14. This
provides an Output High Voltage of 4.05V, and a low of about 3.3V to the
fiber module.
The termination network on the FXIP/FXIN inputs of the L84225 must be
modified for operation with 5V modules by adding a third resistor as a
“tap” on the pulldown leg, as shown in Figure 14. This divides down the
voltage seen at the input of the L84225 so that it does not exceed the
range of the input buffer. The pull-up resistor recommended by the 5V
module supplier generally remains the same - usually about 82.5 Ohms
to the 5V supply. The normally recommended 125-Ohm pulldown resistor
must be split into two. The values of this new pair should be 52.3 Ohms
connected to the pull-up resistor and 73.2 Ohms connected from the
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52.3-Ohm resistor to ground, providing a voltage divider function at the
junction of the pair. The junction of these two resistors should be
connected to the FXIP/FXIN and SD_[3:0]/FXEN_[3:0] inputs of the
L84225. This will provide a High PECL logic level of 2.36V and a low of
1.92V, which is sufficient for operation of the L84225. An interface
suitable for operation with 5V fiber transceiver modules is shown below
in Figure 14.
Figure 14
FX Interface to 5V Fiber Modules
VDD=5V
3.3V
61.9
VDD = 3.3V
VDD = 5V
TD
TD-
FXOP
FXON
5V
82.5
Fiber
261
L84220
Transceiver
10/100 TX/FX
Transceiver
RD
RD-
52.3
73.2
82.5
FXIP
SD
FXIN
SD/FXEN
SD_THR
52.3
73.2
15K
10K
4.6 MII Controller Interface
4.6.1 General
The MII controller interface allows the L84225 to connect to any external
Ethernet controller without any glue logic, provided that the external
Ethernet controller has an MII interface that complies with IEEE 802.3 as
shown in Figure 11 and Figure 12.
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The L84225 also offers RMII (Reduced MII) interface as a selectable
option for use with controllers (MACs) supporting RMII operation. By
holding the RMII_EN pin high, the RMII interface is enabled, cutting the
required interface signals from 16 to 6. This is a significant savings in
board interconnect for high port count systems.
For normal MII operation, the RMII_EN pin should be tied to GND. Refer
to the RMII description in Section 2 for details of the interface operation.
4.6.2 Clocks
Standard Ethernet controllers with an MII use TXCLK to clock data in on
inputs TXD[3:0]. TXCLK is specified in IEEE 802.3 and on the L84225
to be an output. The L84225 requires a 25 MHz reference frequency in
MII mode, and 50 MHz in RMII mode. This reference frequency must be
applied to the CLKIN pin. CLKIN generates TXCLK inside the L84225;
thus, data can be clocked into the L84225 on the rising edge of output
clock TXCLK or on the rising edge of input clock CLKIN.
If a nonstandard controller is used to interface to the L84225, or in
Repeater Applications, there may be a need to clock TXD[3:0] into the
L84225 on the rising edge CLKIN. Where CLKIN is used as the input
clock, TXCLK can be left open or used for another purpose.
4.6.3 MII Disable
The MII outputs can be placed in the high impedance state and inputs
disabled by setting the MII disable bit in the MI serial port Control
register. When this bit is set to the disable state, the TP and FX outputs
are both disabled and transmission is inhibited. The default value of this
bit when the device powers up or is reset is dependent on the device
address. If the device address latched into PHYAD[4:0] at reset is 11111,
it is assumed that the device is being used in applications where there
maybe more than one device sharing the MII bus, like external PHYs or
adapter cards, so the device powers up with the MII interface disabled.
If the device address latched into PHYAD[4:0] at reset is not 11111, it is
assumed that the device is being used in an application where it is the
only device on the MII bus, like hubs, so the device powers up with the
MII interface enabled.
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4.7 FBI Controller Interface
The FBI (Five Bit Interface) controller interface has the same
characteristics of the MII except that the data path is five bits wide,
instead of 4 bits wide per the MII. The five-bit-wide data path is
automatically enabled when the 4B5B encoder is bypassed. Because of
this encoder/ decoder bypass, the FBI is used primarily for repeaters or
other applications where the PHY encoding/decoding function is not
needed. For more details about the FBI, see the Non-MII Based
Repeaters Section.
4.8 Repeater Applications
4.8.1 MII Based Repeaters
The L84225 can be used as the physical interface for MII based
repeaters by using the standard MII/RMII as the interface to the repeater
core.
For most repeaters, it is necessary to disable the internal CRS loopback.
This can be done by asserting the repeater input of the chip.
For some particular types of repeaters, it may be desirable to either
enable or disable AutoNegotiation, force Half Duplex operation, and
enable either 100 Mbps or 10 Mbps operation. All of these modes can
be configured by either asserting the appropriate hardware pins or by
setting the appropriate bits in the MI serial port Control register.
4.8.2 Clocks
Normally, transmit data sent over the MII/RMII/FBI is clocked into the
L84225 by the rising edge of the output clock TXCLK. It may be desirable
or necessary in some repeater applications to clock in transmit data from
a master clock from the repeater core. This would require that transmit
data be clocked in on the edge of an input clock. An input clock is
available for clocking in data on TXD by the rising edge on the CLKIN
pin. Notice from the timing diagrams that CLKIN generates TXCLK, and
TXD data is clocked in on TXCLK edges. This means that TXD data is
also clocked in on the CLKIN edge as well. Thus, an external clock
driving the CLKIN input can also be used as the clock for TXD.
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4.9 Serial Port
4.9.1 General
The L84225 has an MI serial port to set all of the devices' configuration
inputs and read out the status outputs. Any external device that has an
IEEE 802.3 compliant MI interface can connect directly to the L84225
without any glue logic, as shown in Figure 11 and Figure 12.
As described earlier, the MI serial port consists of five lines: MDC, MDIO,
and PHYAD[4:2]. However, only 2 lines, MDC and MDIO, are needed to
shift data in and out.
PHYAD[4:2] define the three most significant bits of the PHY address, as
described in Section 4.9.3, “Serial Port Addressing,” page 83.
4.9.2 Polling vs. Interrupt
The status output bits can be monitored by either polling the serial port
or with the interrupt output.
If polling is used, the registers can be read at regular intervals and the
status bits can be checked against their previous values to determine any
changes. To make polling simpler, all the registers can be accessed in a
single read or write cycle by setting the register address bits REGAD[4:0]
to 11111 and adding enough clocks to read out all the bits, provided the
multiple register access feature has been enabled.
4.9.3 Serial Port Addressing
The device address for the MI serial port is selected by connecting the
PHYAD[4:2] pins to the desired value. The PHYAD[1:0] addresses are
internally hardwired for each channel as shown in both Table 6 and
Table 8.
4.10 Unmanaged Port Configuration
The L84225 has configuration inputs which can “over-ride” the default
configuration state obtained on POWER-UP or RESET of the device.
Use of these pins ANEG, SPEED_[3:0], and DPLX_[3:0] allow selection
of Global AutoNegotiation, Individual Port Speed (10/100), and Individual
Port Duplex (Full/Half), by properly strapping these pins to VDD or VSS
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as shown in Table 24. Note that these pins should not float, but must be
connected either High or Low for proper operation.
In order to obtain the “Default Mode of Operation”, i.e.: Auto-negotiation
enabled, 100MBs, and Half Duplex; the ANEG, SPEED_[3:0], and
DPLX_[3:0] pins should be set to 1,1,0 respectively.
Table 24
Hardware Configuration
Auto-Negotiate Speed
Configuration
State
Duplex
Advertise 10/100 Advertise Full/Half
Normal
Enabled
(POC/RESET)
Config Pins
ANEG=1
SPEED_[3:0]=1
10MBs
DPLX_[3:0]=0
Full
Complement State Disabled
Config Pins ANEG=0
SPEED_[3:0]=0
DPLX_[3:0]=1
4.11 Long Cable
IEEE 802.3 specifies that 10BaseT and 100BaseTX operate over twisted
pair cable lengths from 0 to 100 meters. The squelch levels can be
reduced by 4.5 dB if the receive level adjust bit is appropriately set in the
MI serial port Channel Configuration register, which will allow the L84225
to operate with up to 150 meters of twisted pair cable. The equalizer is
already designed to accommodate between 0 to 150 meters of cable.
4.12 Clock
The L84225 requires a 25 MHz reference frequency for internal signal
generation in MII mode, and 50 MHz in RMII mode. The appropriate
reference frequency must be applied to the CLKIN pin.
4.13 LED Drivers
The LED[3:0] outputs can all drive LED’s tied to VDD as shown in
Figure 11 and Figure 12. In addition, the LED[3:0] outputs can drive
LEDs tied to GND as well. The LED definitions assume that the LED
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outputs are tied to VDD, active low signals (otherwise the LED outputs
will indicate their respective opposite events.)
The LEDDEF pin determines the default settings for LED[3:0]. If LEDDEF
= 0, the default functions for LED[3:0] are Link 100, Activity, Full Duplex,
and Link 10, respectively. If LEDDEF = 1, the LED functions for LED[3:0]
are forced to LINK + ACTIVITY, Collision, Full Duplex and 10/100 Mbps
operation, respectively. Table 4 defines the LED functions. Table 5
defines the LED events.
The LED[3:0] outputs can also drive other digital inputs. Thus, LED[3:0]
can also be used as digital outputs whose function can be user defined
and controlled through the MI serial port.
4.14 5V Compatible I/O Operation
The input and output pins of the L84225 are tolerant of signal levels up
to a maximum of 5.5V (including overshoot etc.). This allows the
transceiver to be operated with 5V controllers that have TTL I/O
characteristics (0.8 to 2.0V Input levels) without the use of levelshifters
or other interfaces.
Controllers and other system components may be operated with 5V
supplies and all inter-chip signals may be connected directly to the
L84225. All required external logic levels must retain TTL compatibility
since the L84225 outputs are not guaranteed to achieve higher than 2.3V
with a load of 10ma. However, the inputs of the L84225 will tolerate TTL
or CMOS logic levels being driven into the device.
This should make replacement of the Physical Layer transceivers in
existing designs quite simple since any 5V devices do not need to be
changed.
4.15 Power Supply Decoupling
There are 18 VDDs and 19 GNDs on the L84225.
All VDDs on each individual side should be connected together
(grouped) and tied to a power plane, as close as possible to the L84225
supply pins. If the VDDs vary in potential by even a small amount, noise
and latchup can result. The L84225 VDD pins should be kept to within
50 mV of each other.
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All GNDs should be connected as close as possible to the device with a
large ground plane. If the GNDs vary in potential by even a small
amount, noise and latchup can result. The GND pins should be kept to
within 50 mV of each other.
A 0.01-0.1uF decoupling capacitor should be connected between the
VDD group and GND on each of the 4 sides of the L84225 as close as
possible to the device pins, preferably within 0.5 in. The value should be
chosen depending on whether the noise from VDD-GND is high or low
frequency. A conservative approach would be to use two decoupling
capacitors on each side, one 0.1uf for low frequencies, and one 0.001 uf
for high frequency noise on the power supply.
The VDD connection to the transmit transformer center tap shown in
Figure 11 and Figure 12 must be well decoupled in order to minimize
common mode noise injection from the supply into the twisted pair cable.
It is recommended that a 0.01 uF decoupling capacitor be placed
between the transformer center tap VDD connection and the L84225
GND plane. This decoupling capacitor should be physically placed as
close as possible to the transformer center tap, preferably within 0.5 in.
The PCB layout and power supply decoupling discussed above should
provide sufficient decoupling to achieve the following when measured at
the device:
1. the resultant AC noise voltage measured across each VDD/GND set
should be less than 100 mVpp,
2. all VDDs should be within 50 mVpp of each other, and
3. all GNDs should be within 50 mVpp of each other.
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5 Specifications
5.1 Absolute Maximum Ratings
Absolute maximum ratings are limits beyond which may cause
permanent damage to the device or affect device reliability. All voltages
are specified with respect to GND, unless otherwise specified.
•
•
•
•
•
•
•
V
Supply Voltage
-0.3 V to +4.0 V
-0.3 V to 5.5 V
3.0 Watt @ 70 C
-65 to +150 C
-10 to +80 C
DD
All Inputs and Outputs
Package Power Dissipation
Storage Temperature
Temperature Under Bias
Lead Temperature (Soldering, 10 Sec) 260 C
Body Temperature (Soldering, 30 Sec) 220 C
Note that all inputs and outputs are 5V tolerant.
Specifications
Copyright © 1999-2002 by LSI Logic Corporation. All rights reserved.
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5.2 DC Electrical Characteristics
Unless otherwise noted, all test conditions are as follows:
1. T = 0 to +70 C
A
2. V = 3.3 V 5%
DD
3. 25 MHz 0.01%
4. REXT = 10K 1%,no load
Limit
Sym. Parameter
Min
Typ
Max
Unit
Conditions
VIL
VIH
IIL
Input Low Voltage
0.8
Volt
Volt
uA
Input High Voltage
Input Low Current
2
1
VIN = GND
All Except RESET
10
50
1
uA
uA
VIN = GND RESET
VIN = VDD
IIH
Input High Current
VOL Output Low
Voltage
0.4
1
Volt
Volt
Volt
IOL = -4 mA, Except LED[3:0]
IOL = -20 mA, LED[3:0]
VOH Output High
Voltage
VDD -1.0
IOH = 4 mA
All Except LED[3:0]
VDD -1.0
2.4
Volt
Volt
pF
IOH = 10 mA, LED[3:0]
IOH = 10 uA
CIN
IDD
Input Capacitance
5
VDD Supply
Current
450
450
700
mA
mA
mA
Transmitting 100%, 100 Mbps
Transmitting 100%, 10 Mbps
IGND GND Supply
Current
Transmitting 100%, 100 Mbps,
Note 1
700
200
mA
uA
Transmitting 100%, 10 Mbps,
Note 1
Powerdown
Note 1. IGND includes current flowing into GND from the external
resistors and transformer on TPOP/TPON, as shown in Figure 11.
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5.3 Twisted Pair Characteristics, Transmit
Unless otherwise noted, all test conditions are as follows:
1. T = 0 to +70 C
A
2. V = 3.3 V 5%
DD
3. 25 MHz 0.01%
4. REXT = 10K 1%,no load
5. TPOP/N loading shown in Figure 11, or equivalent
Limit
Sym. Parameter
TOV TP Differential Output
Min
Typ
Max
Unit
Conditions
0.950 1.000 1.050
V pk
100 Mbps, UTP Mode, 100
Ohm load
Voltage
1.165 1.225 1.285
V pk
V pk
V pk
%
100 Mbps, STP Mode, 150
Ohm load
2.2
2.5
2.8
10 Mbps, UTP Mode, 100 Ohm
load
2.694 3.062 3.429
10 Mbps, STP Mode, 150 Ohm
load
TOVS TP Differential Output
Voltage Symmetry
98
102
100 Mbps, ratio of positive and
negative amplitude peaks on
TPOP/N
TORF TP Differential Output
Rise And Fall Time
3.0
5.0
0.5
ns
ns
100 Mbps
TORFS TP Differential Output
Rise And Fall Time
Symmetry
100 Mbps, difference between
rise and fall times on TPOP/N
TODC TP Differential Output
Duty Cycle Distortion
0.25
ns
100 Mbps, output data=0101...
NRZI Pattern Unscrambled,
measure at 50% Points
TOJ
TP Differential Output
Jitter
0.7
5.0
ns
%
100 Mbps, Output Data=Scram-
bled /H/
TOO
TP Differential Output
Overshoot
100 Mbps
10 Mbps
10 Mbps
TOVT TP Differential Output
Voltage Template
See Figure 4
See Figure 6
TSOI
TP Differential Output
SOI Voltage Template
Specifications
Copyright © 1999-2002 by LSI Logic Corporation. All rights reserved.
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Limit
Sym. Parameter
Min
Typ
Max
Unit
Conditions
TLPT
TOIV
TOIA
TP Differential Output
Link Pulse Voltage
Template
See Figure 7
10 Mbps, NLP and FLP
TP Differential Output
Idle Voltage
50
42
mV
10 Mbps, Measured on Sec-
ondary Side of Xfmr in
Figure 11
TP Output Current
38
40
mA pk 100 Mbps, UTP with
TLVL[3:0]=1000
31.06 32.66 34.26 mA pk 100 Mbps, STP with
TLVL[3:0]=1000
88
100
112
mA pk 10 Mbps, UTP with
TLVL[3:0]=1000
71.86 81.64 91.44 mA pk 10 Mbps, STP with
TLVL[3:0]=1000
TOIR
TP Output Current
Adjustment Range
0.80
1.2
Adjustable with REXT, Relative
to TOIA with REXT=10K
0.86
1.16
Adjustable with TLVL[3:0]. See
Section 4.3, “TP Transmit Out-
put Current Set.” Relative to
Value at TLVL[3:0]=1000.
TORA TP Output Current
TLVL Step Accuracy
50
%
Relative to Ideal Values in Table
2. Values Relative to Output
with TLVL[3:0]=1000.
TOR
TOC
TP Output Resistance
10K
15
Ohm
pF
TP Output
Capacitance
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5.4 Twisted Pair Characteristics, Receive
Unless otherwise noted, all test conditions are as follows:
1. T = 0 to +70 C
A
2. V = 3.3 V 5%
DD
3. 25 MHz 0.01%
4. REXT = 10K 1%,no load
5. 62.5/10 MHz Square Wave on TP inputs in 100/10 Mbps
Limit
Sym. Parameter
RST TP Input Squelch
Min
Typ
Max
Unit
Conditions
166
310
60
500
540
200
378
300
324
180
227
mV pk 100 Mbps, RLVL=0
mV pk 10 Mbps, RLVL=0
mV pk 100 Mbps, RLVL=1
mV pk 10 Mbps, RLVL=1
mV pk 100 Mbps, RLVL=0
mV pk 10 Mbps, RLVL=0
mV pk 100 Mbps, RLVL=1
mV pk 10 Mbps, RLVL=1
Threshold
217
100
186
60
RUT
TP Input Unsquelch
Threshold
130
ROCV TP Input Open Circuit
Voltage
VDD - 2.4
0.2
Volt
Volt
Volt
Voltage on either
TPIP or TPIN with
respect to GND
RCMR TP Input Common Mode
Voltage Range
ROCV
0.25
Voltage on either
TPIP or TPIP with
respect to GND
RDR
TP Input Differential Volt-
age Range
VDD
RIR
RIC
TP Input Resistance
TP Input Capacitance
5K
ohm
pF
10
Specifications
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April, 2002
5.5 Fiber Interface Characteristics, Transmit and Receive
Unless otherwise noted, all test conditions are as follows:
1. T = 0 to +70 C
A
2. V = 3.3 V 5%
DD
3. 25 MHz 0.01%
4. REXT = 10K 1%,no load
5. FXOP/N loading shown in Figure 12 or equivalent
Limit
Sym.
Parameter
Min
Typ
Max
Unit Conditions
FOVH
Fiber Output Level,
High
VDD
1.020
-
VDD
0.880
-
V
V
V
V
V
Single ended FXOP/N rela-
tive to GND
FOVL
FDIV
FCMR
FSDIH
Fiber Output Level,
Low
VDD
1.810
-
VDD
1.620
-
Single ended FXOP/N rela-
tive to GND
Fiber Differential
Input Voltage
0.150
FXIP/N
Fiber Input Common
Mode Voltage Range
1.35
VDD-0.8
FXIP/N
SD/FXEN Input High VSD_THR
Voltage
This spec applies when
device is connected to 5 V
external fiber optic trans-
ceivers. VSD_THR is the
-50 mV
voltage applied to the
SD_THR pin and is spec’ed
by FSDTHR
.
VCC -
1.165
V
This spec applies when
device is connected to 3.3V
external fiber optic trans-
ceivers. SD_THR is tied to
GND.
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Limit
Typ
Sym.
Parameter
Min
Max
Unit Conditions
V This spec applies when
FSDIL
SD/FXEN Input Low
Voltage
VSD_THR
+50 mV
device is connected to 5V
external fiber optic trans-
ceivers. VSD_THR is the
voltage applied to the
SD_THR pin and is spec’ed
by FSDTHR.
VCC-
1.475
This spec applies when
device is connected to 3.3V
external fiber optic trans-
ceivers. SD_THR is tied to
GND.
FSDTHR SD_THR Input
Voltage
VCC
–1.3 V
–10%
VCC
1.3 V
VCC
–1.3 V
+10%
V
This spec applies when
device is connected to 5V
external fiber optic trans-
ceivers. When interfacing to
3.3V fiber optic transceiv-
ers, SD_THR is tied to
GND.
FDIS
Fiber Interface Dis-
able Voltage,
SD/FXEN Pin
0.45
0.45
0.85
0.85
V
V
For disabling fiber interface
FLVL
Internal/External
Signal Detect Level
Select, SD_THR Pin
For selecting interface to
either 3.3V or 5 V external
fiber transceivers
5.6 AC Test Timing Conditions
Unless otherwise noted, all test conditions are as follows:
1. T = 0 to +70 C
A
2. V = 3.3 V 5%
DD
3. 25 MHz 0.01%
4. REXT = 10K 1%,no load
5. Input conditions:
All inputs:
tr,tf <= 10 ns, 20-80%
6. Output Loading
TPOP/N:
Same as Figure 11 or equivalent, 10 pF
REGDEF:
All other digital outputs:
1K pullup, 50 pF
25 pF
Specifications
Copyright © 1999-2002 by LSI Logic Corporation. All rights reserved.
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April, 2002
7. Measurement Points:
TPOP/N, TPIP/N:
0V during data, 0.3V at start/end of packet
1.4 V
All other inputs and outputs:
5.7 Clock Timing Characteristics
Refer to Figure 15 for Timing Diagram
Limit
Sym. Parameter
Min
Typ
Max
Unit Conditions
t1
t2
t3
t4
CLKIN Period
39.996
40
20
40.004
20.002
ns
ns
ns
ns
ns
ns
ns
ns
MII
19.996
RMII
CLKIN High Time
CLKIN Low Time
CLKIN to TXCLK Delay
16
7
MII
RMII
16
7
MII
RMII
10
20
100 Mbps, MII
10 Mbps, MII
Figure 15
Output Timing
t1
t2
t3
OSCIN
t4
TXCLK
(100 MB)
t4
t4
TXCLK
(10 MB)
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5.8 Transmit Timing Characteristics
Refer to Figure 16 and Figure 17 for Timing Diagram
Limit
Typ
Sym. Parameter
Min
Max
Unit
Conditions
t11
t12
t13
TXCLK Period
39.996
399.96
16
40
400
20
40.004
400.04
24
ns
ns
ns
ns
ns
ns
ns
ns
ns
ns
ns
ns
ns
ns
ns
ns
100 Mbps
10 Mbps
100 Mbps
10 Mbps
100 Mbps
10 Mbps
TXCLK Low Time
TXCLK High Time
160
200
20
240
24
16
160
200
240
10
t14
t15
TXCLK Rise/Fall Time
TXEN Setup Time
15
4
MII
RMII
t16
t17
t18
t19
t20
TXEN Hold Time
0
MII
2
MII
CRS During Transmit Assert
Time
40
100 Mbps, MII and FBI
400
160
900
10 Mbps, MII and FBI
CRS During Transmit Deas-
sert Time
100 Mbps
10 Mbps
MII
TXD Setup Time
15
4
RMII
TXD Hold Time
0
ns
MII
2
RMII
t21
t22
TXER Setup Time
TXER Hold Time
15
0
ns
ns
MII
2
RMII
t23
Transmit Propagation Delay
Transmit Output Jitter
60
140
140
600
0.7
ns
ns
ns
100 Mbps, MII
100 Mbps, FBI
10 Mbps
t24
ns pk-pk 100 Mbps
ns pk-pk 10 Mbps
5.5
t25
Transmit SOI Pulse Width
To 0.3V
250
ns
10 Mbps
Specifications
Copyright © 1999-2002 by LSI Logic Corporation. All rights reserved.
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Limit
Typ
Sym. Parameter
Min
Max
Unit
Conditions
t26
t27
t28
Transmit SOI Pulse Width to
40 mV
4500
ns
10 Mbps
LEDn Delay Time
25
ms
ms
LEDn Programmed
For Activity
LEDn Pulse Width
80
105
LEDn Programmed
For Activity
Figure 16
Transmit Timing - 100 Mbps
MII 100 Mbps
t
11
TXCLK
TXEN
t
t
13
t
t
14
15
16
t
12
t
14
t
t
18
17
CRS
t
20
t
19
TXD[3:0]
N0
N1
t
N2
N3
t
21
22
TXER
t
t
24
23
TPO
±
IDLE
IDLE
/J/K/
DATA
/T/R/
IDLE
t
27
t
28
LEDn
RMII 100 Mbps
Same as MII 100 Mbps except:
1. Data Input on TXD[1:0]; TXD[3:2] Not Used.
2. All Timing Referenced to CLKIN instead of TXCLK
FBI 100 Mbps
Same as MII 100 Mbps except:
1. TXER Converted to TXD4.
2. RXER Converted to RXDA
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Figure 17
Transmit Timing - 10 Mbps
MII 10 Mbps
t
11
TXCLK
TXEN
t
t
13
14
t
t
t
15
16
12
t
14
t
t
18
17
CRS
t
20
t
19
TXD[3:0]
N0
N1
N2
N3
t
26
t
24
t
t
25
23
PREAMBLE
PREAMBLE
TP0
±
DATA
DATA
SOI
t
27
t
28
LEDn
RMII 10 Mbps
Same as MII 10 Mbps except:
1. Data Input on TXD[1:0]; TXD[3:2] Not Used.
2. All Timing Referenced to CLKIN instead of TXCLK.
3. Each data Di-Bit on TXD[1:0] is present for 10 consecutive CLKIN cycles.
Specifications
Copyright © 1999-2002 by LSI Logic Corporation. All rights reserved.
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April, 2002
5.9 Receive Timing Characteristics
Refer to Figure 18 through Figure 24 for Timing Diagrams
Limit
Typ
Sym. Parameter
t31 Start of Packet to CRS
Min
Max
Unit
Conditions
200
200
700
240
280
600
ns
ns
ns
ns
ns
ns
100 Mbps, MII
100 Mbps, RMII
10 Mbps
Assert Delay
t32
End of Packet to CRS
Deassert Delay
130
100 Mbps, MII
100 Mbps RMII
10 Mbps, MII. Relative to Start
of SOI Pulse
1000
ns
10 Mbps, RMII. Relative to
Start of SOI Pulse
t33
Start of Packet to
RXDV Assert Delay
240
3600
280
ns
ns
ns
ns
ns
100 Mbps
10 Mbps
t34
End of Packet to
RXDV Deassert Delay
100 Mbps, MII
100 Mbps, RMII
360
1000
10 Mbps, MII. Relative to Start
of SOI Pulse
2800
ns
10 Mbps, RMII. Relative to
Start of SOI Pulse
t37
RXCLK to RXDV RXD,
RXER Delay
-8
-4
8
ns
ns
ns
ns
ns
ns
ns
ns
100 Mbps, MII
100 Mbps and 10 Mbps, RMII
10 Mbps, MII
100 Mbps
2
-80
18
80
t38
t39
t40
RXCLK High Time
RXCLK Low Time
20
200
20
22
180
18
600
22
10 Mbps
100 Mbps
180
125
200
600
200
10 Mbps
SOI Pulse Minimum
Width Required for
Idle Detection
10 Mbps
Measured TPIP/N from last
zero cross to 0.3 V point.
t41
Receive Input Jitter
2.0
ns pk-pk 100 Mbps
13.5 ns pk-pk 10 Mbps
25 ms LEDn Programmed for Activity
t43
LEDn Delay Time
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Limit
Typ
Sym. Parameter
t44 LEDn Pulse Width
t45
Min
Max
Unit
Conditions
60
105
10
ms
ns
LEDn Programmed for Activity
RXCLK, RXD, CRS,
RXDV, RXER Output
Rise and Fall Times
Figure 18
Receive Timing, Start of Packet - 100 Mbps, MII & FBI
MII 100 Mbps
TPI
±
IDLE
J
K
DATA DATA DATA DATA DATA DATA DATA DATA DATA DATA DATA DATA DATA
DATA DATA DATA DATA DATA
t
41
t
31
CRS
t
39
t
38
RXCLK
RXDV
TX
TX
TX
TX
TX
RX
RX
RX
RX
RX
RX
t
37
t
33
t
37
RXD[3:0]
PREAMBLE PREAMBLE PREAMBLE PREAMBLE PREAMBLE
t
t
37
37
RXER
t
t
44
43
PLEDn
FBI 100 Mbps
Same as MII 100 Mbps except:
1. RXER Converted to RXD4.
2. TXER Converted to TXD4.
Specifications
Copyright © 1999-2002 by LSI Logic Corporation. All rights reserved.
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Figure 19
Receive Timing, Start of Packet - 100 Mbps, RMII
RMII 100 Mbps
TPI
±
IDLE
J
K
DATA DATA DATA DATA DATA DATA DATA DATA DATA DATA DATA DATA DATA
DATA DATA DATA DATA DATA
t
41
t
31
CRS
t
39
t
38
CLKIN
RXDV
TX
TX
TX
TX
TX
RX
RX
RX
RX
RX
RX
t
37
t
33
t
37
RXD[1:0]
PREAMBLE PREAMBLE PREAMBLE PREAMBLE PREAMBLE
t
37
t
37
RXER
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Figure 20
Receive Timing, End of Packet - 100 Mbps
MII 100 Mbps
DATA
T
R
I
I
I
I
I
I
I
I
I
I
I
I
I
I
I
I
I
I
I
TPI
±
t
32
CRS
t
39
t
38
RXCLK
RX
RX
RX
RX
34
RX
RX
RX
RX
TX
TX
t
37
t
RXDV
RXD[3:0]
DATA
DATA
DATA
DATA
DATA
DATA
DATA
RMII 100 Mbps
TPI
±
DATA
T
R
I
I
I
I
I
I
I
I
I
I
I
I
I
I
I
I
I
I
I
t
32
34
CRS
t
t
t
39
37
t
t
38
37
CLKIN
RX
RX
RX
RX
RX
RX
RX
RX
TX
TX
RXD[1:0]
DATA
DATA
DATA
DATA
DATA
DATA
DATA
Specifications
Copyright © 1999-2002 by LSI Logic Corporation. All rights reserved.
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Figure 21
Receive Timing, Start of Packet - 10 Mbps, MII
MII 10 Mbps
t
41
DATA
DATA
TPI
±
t
31
CRS
t
39
t
38
RXCLK
TX
TX
TX
TX
TX
RX
RX
RX
RX
RX
RX
t
37
t
33
RXDV
RXD[3:0]
RXER
t
37
PREAMBLE PREAMBLE
DATA
DATA
DATA
t
t
43
44
LEDn
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Figure 22
Receive Timing, Start of Packet - 10 Mbps, RMII
RMII 10 Mbps
t
41
DATA
DATA
TPI
±
t
31
CRS
t
39
t
38
CLKIN
TX
TX
TX
TX
TX
RX
RX
RX
RX
RX
RX
t
t
37
33
PREAMBLE PREAMBLE
DATA DATA
DATA
DATA
RXD[1:0]
RXER
Note 1
t
t
43
44
LEDn
Note 1. Each Di-Bit is present on RXD[1:0] for 10 consecutive CLKIN cycles.
Specifications
Copyright © 1999-2002 by LSI Logic Corporation. All rights reserved.
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April, 2002
Figure 23
Receive Timing, End of Packet - 10 Mbps, MII
MII 10 Mbps
t
41
SOI
DATA
TPI
±
DATA
DATA DATA DATA
t
40
t
32
CRS
t
39
t
38
RXCLK
RX
RX
RX
RX
RX
RX
RX
RX
TX
TX
t
37
t
34
RXDV
RXD[3:0]
DATA
DATA
DATA
DATA
DATA
DATA
DATA
Figure 24
Receive Timing, End of Packet - 10 Mbps, RMII
RMII 10 Mbps
t
41
SOI
DATA
TPI
±
DATA
DATA DATA DATA
t
40
t
32
CRS
t
34
t
37
t
39
t
38
CLKIN
RX
RX
RX
RX
RX
RX
RX
RX
TX
TX
RXD[3:0]
DATA
DATA
DATA
DATA
DATA
DATA
DATA
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5.10 Collision Timing Characteristics
Refer to Figure 25, Figure 26, and Figure 27 for Timing Diagrams
Limit
Typ
Sym. Parameter
Min
Max
Unit Conditions
t51
t52
t53
t54
Rcv Packet Start to COL
Assert Time
200
700
240
300
200
700
240
300
25
ns
ns
ns
ns
ns
ns
ns
ns
ms
100 Mbps
10 Mbps
100 Mbps
10 Mbps
100 Mbps
10 Mbps
100 Mbps
10 Mbps
Rcv Packet Stop to COL Deas-
sert Time
130
Mt Packet Start to COL Assert
Time
Xmt Packet Stop to COL Deas-
sert Time
t55
t56
LEDn Delay Time
LEDn Pulse Time
LEDn programmed for
collision
80
105
ms
LEDn programmed for
collision
t57
t58
Collision Test Assert Time
Collision Test Deassert Time
5120
40
ns
ns
ns
ns
800
10
10 Mbps
t60
COL Rise and Fall Time
Specifications
Copyright © 1999-2002 by LSI Logic Corporation. All rights reserved.
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April, 2002
Figure 25
Collision Timing, Receive
MII 100 Mbps
t
41
SOI
DATA
TPI
±
DATA
DATA DATA DATA
t
40
t
32
CRS
t
39
t
38
RXCLK
RX
RX
RX
RX
RX
RX
RX
RX
TX
TX
t
37
t
34
RXDV
RXD[3:0]
DATA
DATA
DATA
DATA
DATA
DATA
DATA
FBI 100 Mbps
Same as MII 100 Mbps
MII 100 Mbps
TPO
TPI
±
±
t
t
52
51
COL
t
t
56
55
LEDn
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Figure 26
Collision Timing, Transmit
MII 100 Mbps
TPO
±
±
I
I
DATA DATA DATA DATA DATA DATA DATA DATA DATA DATA DATA DATA DATA
I
I
I
J
K
DATA DATA DATA DATA
T
R
I
I
TPI
t
t
52
51
COL
t
t
56
55
LEDn
FBI 100 Mbps
Same as MII 100 Mbps
MII 100 Mbps
TPO
±
±
TPI
t
t
52
51
COL
t
t
56
55
LEDn
Figure 27
Collision Test Timing
MII 100 MB
TXEN
COL
t
t
58
57
Specifications
Copyright © 1999-2002 by LSI Logic Corporation. All rights reserved.
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5.11 Link Pulse Timing Characteristics
Refer to Figure 28 and Figure 29 for Timing Diagrams
Limit
Typ
Sym. Parameter
Min
Max
Unit
Conditions
t61
t62
t63
NLP Transmit Link Pulse Width
See Figure 8
ns
ms
ns
NLP Transmit Link Pulse Period
8
24
NLP Receive Link Pulse Width
Required For Detection
50
t64
t65
t66
NLP Receive Link Pulse Mini-
mum Period Required For
Detection
6
7
ms
ms
link_test_min
NLP Receive Link Pulse Maxi-
mum Period Required For
Detection
50
150
link_test_max
link_loss
NLP Receive Link Pulses
Required To Exit Link Fail State
3
3
3
Link
Pulses
lc_max
t67
t68
FLP Transmit Link Pulse Width
100
150
ns
FLP Transmit Clock Pulse To
Data Pulse Period
55.5 62.5 69.5
µs
interval_timer
t69
t70
t71
t72
FLP Transmit Clock Pulse To
Clock Pulse Period
111
8
125
139
22
µs
ms
ns
FLP Transmit Link Pulse Burst
Period
transmit_link_burst_timer
FLP Receive Link Pulse Width
Required For Detection
50
5
FLP Receive Link Pulse Minimum
Period Required For Clock Pulse
Detection
25
185
47
µs
flp_test_min_timer
t73
t74
t75
t76
FLP Receive Link Pulse Maxi-
mum Period Required For Clock
Pulse Detection
165
15
µs
µs
µs
flp_test_max_timer
FLP Receive Link Pulse Minimum
Period Required For Data Pulse
Detection
data_detect_min_timer
data_detect_max_timer
FLP Receive Link Pulse Maxi-
mum Period Required For Data
Pulse Detection
78
100
17
FLP Receive Link Pulses
Required To Detect Valid FLP
Burst
17
Link
Pulses
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Limit
Typ
Sym. Parameter
Min
Max
Unit
Conditions
t77
t78
t79
FLP Receive Link Pulse Burst
Minimum Period Required For
Detection
5
7
ms
nlp_test_min_timer
FLP Receive Link Pulse Burst
Maximum Period Required For
Detection
50
3
150
3
ms
nlp_test_max_timer
FLP Receive Link Pulses Bursts
Required To Detect AutoNegotia-
tion Capability
3
Link
Pulse
Bursts
t80
t81
t82
FLP Receive Acknowledge Fail
Period
1200
1200
750
1500
1500
1000
ms
ms
ms
FLP Transmit Renegotiate Link
Fail Period
break_link_timer
NLP Receive Link Pulse Maxi-
mum Period Required For
Detection After FLP Negotiation
Has Completed
link_fail_inhibit_timer
Figure 28
NLP Link Pulse Timing
a. Transmit NLP
TPO±
t
61
t
62
b. Receive NLP
TPI±
t
63
t
64
t
t
66
65
PLEDn
Specifications
Copyright © 1999-2002 by LSI Logic Corporation. All rights reserved.
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Figure 29
FLP Link Pulse Timing
a. Transmit FLP and Transmit FLP Burst
CLK
DATA
CLK
DATA
CLK
CLK
DATA
TPO±
t
67
t
68
t
69
t70
b. Receive FLP
CLK
DATA
CLK
DATA
TPI±
31.25 62.50
93.75
125.00
156.25
t
71
t
72
t
73
t
74
t
75
c. Receive FLP Burst
TPI±
t
t
t
78
79
77
LEDn
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5.12 Jabber Timing Characteristics
Refer to Figure 30 for Timing Diagram
Limit
Typ
Sym. Parameter
t91 Jabber Activation Delay Time
t92 Jabber Deactivation Delay Time
Min
Max
Unit
Conditions
50
100
750
ms
ms
10 Mbps
10 Mbps
250
Figure 30
Jabber Timing
MII 100 Mbps
Not applicable
FBI 100 Mbps
MII 10 Mbps
TXEN
Not applicable
t
t
t
91
91
91
TPO
±
t
92
COL
CRS
Specifications
Copyright © 1999-2002 by LSI Logic Corporation. All rights reserved.
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5.13 LED Driver Timing Characteristics
Refer to Figure 31 for Timing Diagram
Limit
Sym. Parameter
Min
Typ
Max
Unit
Conditions
t96
t97
LED[3:0] On Time
LED[3:0] Off Time
80
80
105
105
ms
ms
LED[3:0] Programmed to Blink
LED[3:0] Programmed to Blink
Figure 31
LED Driver Timing
t
t
96
97
LED[5:0]
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L84225 Quad 100BaseTX/FX/10BaseT Phys. Layer Device - Technical Manual
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5.14 MI Serial Port Timing Characteristics
Refer to Figure 32 for Timing Diagram
Limit
Sym. Parameter
Min
Typ
Max
Unit
Conditions
t101
t102
t103
t104
t105
t106
t107
t108
MDC High Time
20
20
10
10
ns
ns
ns
ns
ns
ns
ns
MDC Low Time
MDIO Setup Time
Write Bits
MDIO Hold Time
Write Bits
MDC To MDIO Delay
MDIO Hi-Z To Active Delay
MDIO Active To HI-Z Delay
Frame Delimiter (Idle)
20
20
20
Read Bits
Write-Read Bit Transition
Read-Write Bit Transition
32
Clocks # of Consecutive MDC Clocks
with MDIO=1
t110
t111
MDC To MDIO Interrupt
Pulse Assert Delay
100
100
ns
MDC To MDIO Interrupt
Pulse Deassert Delay
ns
Figure 32
MI Serial Port Timing
t102
t101
14
MDC
0
1
13
15
16
17
30
31
t104
t103
ST1
t105
t107
t106
MDIO
(READ)
ST0
t104
REGAD0
REGAD0
TA0
D15
D14
D0
TA1
t103
ST1
MDIO
(WRITE)
ST0
TA1
TA0
D15
D1
D0
Specifications
Copyright © 1999-2002 by LSI Logic Corporation. All rights reserved.
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6 Ordering Information
L
84225
/ Z
Manufacturer
Part Type
Product Rev.
Quad 100 Base-TX/FX10 Base-T
Physical Layer Device (PHY)
7 Revision History
March 2, 1999:
•
•
MD400183/– has been changed to MD400183/A
Global: References to JAM have been changed to AD_REV, and
MDINT has been changed to REGDEF.
page 7
•
Pin #98, Row has been completely changed.
page 8
•
Pin #110, I/O, “I Pulldown” has been changed to “I.”
page 9
•
Pin #101, Pin Name RMII_EN has been changed to RMII_EN.
page 12, Figure 1
•
References to JAM and MDINT have been changed to AD_REV and
REGDEF, respectively.
page 55, Section 2.25.7, “Invalid Registers”
Section 2.25.7, “Invalid Registers,” is new.
•
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page 57, Table 8. MI Serial Port Structure
•
Symbol REGAD4[4:0] Definition, “copy, ...If REGDEF pin asserted
and...” has been deleted.
page 59, Table 9. MI Serial Port Register Map
•
•
Bit x.7, 18 Channel Status Output, INT has been changed to 0.
Bit x.10, 4 AutoNegot. Advertisement, 0 has been changed to
PAUSE.
•
Bit x.10, 5 AutoNegot. Remote Capability, 0 has been changed to
PAUSE.
page 64, Table 14 Register 4 - AutoNegotiation Advertisement Register
Definition
•
•
Bit 4.10 has been changed from 0 to PAUSE.
Row 4.10 has been added.
page 65, Table 15 Register 5 - AutoNegotiation Remote Capability
Definition
•
•
Bit 5.10 has been changed from 0 to PAUSE.
Row 5.10 has been added.
page 68, Table 18 Register 18 - Channel Status Output Register
Definition
•
•
Bit 18.7, is now blank.
Row Bit 18.7, Symbol is now blank, Name is now blank, Definition
has been changed to Reserved.
page 73, Figure 11. Typical Switching Hub Port Schematic Using the
L84225 in Twisted Pair Mode
•
References to JAM and MDINT have been changed to AD_REV and
REGDEF, respectively.
page 74, Figure 12. Typical Switching Hub Port Schematic Using the
L84225 in FX Mode with 3.3V Transceivers
•
References to JAM and MDINT have been changed to AD_REV and
REGDEF, respectively.
Revision History
Copyright © 1999-2002 by LSI Logic Corporation. All rights reserved.
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page 105, Section 5.10, “Collision Timing Characteristics”
•
•
Any references to Jam have been deleted.
Row t has been deleted.
59
page 109, Jam Timing figure
Jam Timing figure has been deleted.
page 109, Figure 28. NLP Link Pulse Timing
Figure 28. NLP Link Pulse Timing is new.
April, 2002:
•
•
•
•
•
MD400183/A has been changed to MD400183/B
Document has been reformatted with a standard LSI template.
Tables and Figures have been renumbered to make a continuous
numeric sequence. All internal cross-references to tables and figures
have been updated.
•
•
•
All references to SEEQ have been removed.
All “84225” were changed to “L84225.”
In Section 2.25.6, “Register Structure,” page 54, descriptions of
Global Configuration and Channel Configuration registers were
updated to note that these registers are now reserved.
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L84225 Quad 100BaseTX/FX/10BaseT Phys. Layer Device - Technical Manual
Copyright © 1999-2002 by LSI Logic Corporation. All rights reserved.
8 Surface Mount Packages
Figure 33
160-Pin PQFP
31.20 ± 0.30
28.00 ± 0.20
0.18 ± 0.05
L84225
0.10 MAX
See Detail A
#160
#1
0.25 min.
1.325
Ref.
3.40 ± 0.20
0.30 ± 0.10
0.65 Ref.
4.10 Max.
0 − 8 ˚
Detail A
1. All Dimensions are in millimeters
0.88 ± 0.15
Important:
This drawing may not be the latest version.
Surface Mount Packages
Copyright © 1999-2002 by LSI Logic Corporation. All rights reserved.
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April, 2002
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Doc. No. MD400183/B
April, 2002
Surface Mount Packages
Copyright © 1999-2002 by LSI Logic Corporation. All rights reserved.
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