PJ9910 [ETC]
LED 恒流驱动控制IC; LED恒流驱动控制IC
| 型号： | PJ9910 |
| 厂家： | 
ETC |
| 描述： | LED 恒流驱动控制IC |
| 文件： | 总23页 (文件大小：340K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
Preliminary
PJ9910
LED 恒流驱动控制 IC PJ9910
概述
特性
PJ9910 是一款高效率，稳定可靠的高亮度 LED
灯恒流驱动控制 IC，内置高精度比较器，
off-time 控制电路，恒流驱动等电路，特别适合
大功率，多个高亮度 LED 灯串恒流驱动。
y
可编程的 LED 驱动电流，编程范围为几毫
安到 1 安培
y
y
y
y
y
高效率：优于 90%
宽输入电压范围：2.5V~400V
高工作频率：最大 2.5MHz
工作频率可调：10KHz~2.5MHz
PJ9910 采用固定 off-time 控制工作方式，其工
作频率可高达 2.5MHz，可使外部电感和滤波电
高、体积减少，效率提高。off-time 最小时间，
可通过外部电阻和电感进行设置，工作频率可
根据用户要求而改变。在 EN 端加 PWM 信号，
可调节 LED 灯的亮度。
驱动 LED 灯功能强：LED 灯串可从 1 个到
几百个 LED 高亮度灯
y
亮度可 PWM 可调：通过 EN 端，调节 LED
灯亮度
通过调节外置的电阻，能控制高亮度 LED 灯的
驱动电流，使 LED 灯亮度达到预期恒定亮度，
流过高亮度 LED 灯的电流可从几毫安到 1 安培
变化。
应用范围
y
y
y
y
y
y
y
220V 交流供电 LED 照明灯
订货信息
RGB 大显示屏 LED 灯
220V 交流供电 LED 日光灯
平板显示器 LED 背光灯
交通警示 LED 灯
恒流充电器控制
通用恒流源
封装
1 of 9
Preliminary
PJ9910
典型应用电路图
L
VIN
Bandgap
VDD
Off-
t i me
TOFF
S
Q
DRV
CS
R
Zener
Di ode
2. 5V-
5. 5V
250mV
-
EN
R (opt i on)
DC
+
GND
R
CS
图 1
管脚排列
管脚序号
管脚名称
VSS
功能描述
电源地
1
2
3
4
5
6
7
8
EN
芯片使能端
空脚
NC
GND
DRV
CS
电源地
外部 MOS 驱动脚
输出电流检测
关断时间设置
电源正端
TOFF
VDD
2 of 9
Preliminary
PJ9910
最大额定参数值
参数类型
电压
符号
描述
典型值
单位
Vmax
8
V
VDD 脚最大电压
Vmin-max
Tmin-max
Tstorage
VESD
-0.3-VDD+0.3
-20-85
V
EN 脚、CS 脚和 FB 脚电压范围
工作温度
oC
oC
V
温度
-40-165
2000
存储温度
ESD 抗静电
电气特性
ESD 抗静电能力（人体模式）
参数
符号
VDD
VCS
测试条件
最小
2.5
典型 最大
单位
V
6.5
电源电压
CS 脚反馈电压
工作电流
240
250
0.5
260
1
mV
mA
ns
IDD
TOFF0
IDDQ
VENH
VENL
TRISE
620
关断时间 (Ｔoff 脚悬空)
待机电流
1
uA
V
2.0
EN 脚逻辑高电平
EN 脚逻辑低电平
DR 脚电平上升时间
DRV 脚电平下降时间
0.8
50
50
V
ns
DRV 脚接 500pF 电容
DRV 脚接 500pF 电容
ns
T
FALL
3 of 9
App Notes(Step Down)
PJ9910
应用指引
一 、 市 电 交 流 220V 供 电 LED 灯 照 明 应 用
高 亮 度 大 功 率 LED 灯 ， 由 于 相 同 亮 度 的 情 况 下 ， 比 白 炽 灯 省 电 约 80%， 得 到 了
广 泛 的 交 流 供 电 照 明 应 用 ， 大 有 逐 渐 替 代 既 耗 电 、 发 热 、 寿 命 短 的 白 炽 灯 的 趋 势 。
PJ 9910 特 别 适 合 110V/ 220V 交 流 供 电 的 照 明 ，典 型 应 用 如 图 2 所 示 ，220V 交 流
电 通 过 整 流 桥 整 流 后 ， 可 获 得 约 400V 的 直 流 电 压 。 由 于 PJ 9910 VDD 供 电 为 5. １ V，
所 以 要 通 过 一 个 电 阻 和 一 个 稳 压 管 给 I C 供 电 。 在 MOSFET 控 制 电 压 为 高 电 平 时 ，
MOSFET 功 率 开 关 管 导 通 ， 电 感 L 储 存 能 量 ， 当 控 制 电 压 为 低 电 平 时 ， MOSFET 关 断 ，
储 能 电 感 通 过 肖 特 基 二 极 管 释 放 能 量 ， 从 而 点 亮 LED 灯 串 。
电 路 参 数 选 择 ：
1） LED 平 均 电 流
在 图 1 工 作 在 连 续 工 作 模 式 下 ， LED 的 平 均 电 流 I L 如 图 2 示 。
T
T
T
OFF
ON
ILMAX
IL
i L(t )
I
ΔL
图 2
I
LMAX 是 通 过 LED 灯 的 最 大 电 流 。
2）工作频率确定
工作频率由接在 T 脚的 R 和 C 来设定，R 接到 VDD 端，R 阻值越小，频率越高，C
OFF
OSC
OSC
OSC
OSC
OSC
越大，工作频率越低。
工作频率的高低，是根据实际使用情况决定的。工作频率越高，电感可以越小，电感的成
本越低。
LED 灯 驱 动 的 占 空 比 为 D=Vout ／ Vi n。 T 为 MOSFET 管接通时间，T 为 MOSFET 管断
ON
OFF
开时间（休 止 期 ）。休 止 期 计 算 公 式 如 下 ：
100KΩ• ROFF
T
OFF = 0.51•
•(COFF +10pF)
ROFF +100KΩ
如 TOFF 脚不接电阻电容，则
T
OFF = 0.51•100KΩ•10pF = 510ns
4 of 9
App Notes(Step Down)
PJ9910
1
1− D
电路工作频率计 算 公 式 如 下 ： F =
=
T
T
OFF
如 T 脚接 1000P 电容， T =51ms ， D=0. 1， 则电路工作频率 F 约为 20KHz。
OFF
OFF
3）电感 L 选择
电 感 L 的 选 用 原 则 是 确 保 流 过 电 感 的 电 流 变 化 值 ，远 小 于 通 过 电 感 的 最 大 电 流
值 。 在 正 常 工 作 中 ， 电 感 处 于 一 个 充 电 放 电 的 状 态 ， 当 输 入 电 压 和 输 出 电 压 的 压
差 较 大 时 ， 加 大 电 感 的 值 ， 当 压 差 小 时 ， 可 以 用 较 小 的 电 感 。
为 了 减 少 流 过 电 感 的 电 流 波 动 ，电 路 应 工 作 在 连 续 工 作 模 式 。在 连 续 工 作 模 式
下 ， ΔI L 最 小 。 在 休 止 期 ， 流 过 LED 灯 的 ΔI L 计 算 如 下 ：
VOUT
∆I
L
=
•TOFF
L
为 了 使 流 过 LED 灯 电 流 波 动 小 于 ΔI L，电感值应满足：
VOUT
L ≥
•TOFF
∆IL
一 般 取 值 在 几 百 微 享 到 十 几 毫 享 ， 视 实 际 应 用 而 定 。
4）RCS 阻 值 确 定
RCS 阻 值 不 同 ， 就 可 设 置 通 过 LED 的 驱 动 电 流 ， RCS 越 小 ， 输 出 电 流 越 大 。 RCS
的 选 择 公 式 如 下 ：
250mV
RCS =
I
L
+ 0.5∆I
L
I L 为 通 过 LED 灯 的 平 均 电 流 ； 通 常 ， 波 动 电 流 ΔI L 应 小 于 I L 的 十 分 之 一 。
例 如 ： I L ＝ 350mA， ΔI L＝ 17. 5mA， 则 RCS=0. 68Ω
5） MOSFET 管 的 选 用
在 220V 交 流 供 电 情 况 下 ， 首 先 要 考 虑 MOSFET 的 耐 压 ， 一 般 要 求 MOSFET 的
耐 压 高 于 600V。 其 次 ， 根 据 驱 动 LED 灯 电 流 的 大 小 ， 选 择 MOSFET 的 I DS 最 大 电
流 。
一 般 情 况 下 ， 应 选 用 MOSFET 的 I DS 最 大 电 流 是 LED 灯 驱 动 电 流 的 5 倍 以 上 。
另 外 MOSFET 的 内 阻 要 小 ； RDS 应 小 于 0. 5 欧 以 下 ， RDS 越 小 ， 损 耗 在 MOSFET 管 上
的 功 率 越 小 ， 电 路 的 变 换 效 率 就 越 高 。
为 了 降 低 对 MOSFET 管 的 要 求 ， 可 选 用 图 3 应 用 电 路 图 。
6）LED 灯亮度调节
LED 灯的亮度调节，可由以下二种方法：
第一种方法是通过改变 R 的电阻，R 的电阻越小，LED 灯的亮度越高，R 电阻越大，亮
CS
CS
CS
度越小。
第二种方法是在 EN 端加 PWM 信号调光，PWM 信号可由 CPU 产生，也可由其它脉冲信号
5 of 9
Preliminary
PJ9910
产生，PWM 信号可控制通过 LED 灯的电流从 0 变到正常电流状态，即可使 LED 灯从暗变为正常
亮度。PWM 占空比越大，亮度越亮。利用 PWM 控制 LED 的亮度，非常方便和灵活，是最常用的
调光方法，PWM 的频率可从几十 Hz 到几千 KHz。
7）EN 使能端子
在 EN 端接（低电平）地时，PJ9910 处于休眠状态，此时，工作电流小于 10uA，自耗电
非常小，当 EN 端为高电平时，PJ9910 处于工作状态，此时空载工作电流约为 200uA。
EN 端可接受 PWM 信号调光信号，完成调光功能。
6 of 9
Preliminary
PJ9910
典型应用设计
典型应用１：
市电交流220V供电，驱动45串、6并、20mA白光LED灯，输出总电流120mA，使用在LED
日光灯照明，应用电路如图3。改变R4可以改变输出电流大小。
图 3
7 of 9
Preliminary
PJ9910
典型应用 2：
市电交流 220V 供电，驱动 12 颗 1W 白光 LED 灯，使用在 LED 洗墙灯装饰，应用电路如
图 4。
图 4
8 of 9
Preliminary
PJ9910
封装信息
9 of 9
P.1
PJ9910
WIDE INPUT RANGE
POWER LED DRIVER
DESCRIPTION
FEATURES
z >90% Efficiency
z 8V to 450V input range
The PJ9910 is a PWM high-efficiency LED
driver control IC. It allows efficient
z Constant-current LED driver
z Applications from a few mA to more than 1A
output
z LED string from one to hundreds of diodes
z PWM Low-Frequency Dimming via Enable pin
z Input Voltage Surge ratings up to 450V
operation of High Brightness (HB) LEDs
from voltage sources ranging from 8Vdc up
to 450Vdc. The PJ9910 controls an external
MOSFET at fixed switching frequency up to
300 kHz. The frequency can be programmed
using a single resistor. The LED string is
driven at constant current rather than
constant voltage, thus providing constant
light output and enhanced reliability. The
output current can be programmed between
a few milliamperes and up to more than 1A.
APPLICATIONS
z DC/DC LED driver
z Automotive
z Lighting
PAD DIAGRAM
TYPICAL APPLICATION CIRCUIT
1. Chip size: X=1.88mm, Y=1.54mm
(without scribe line width).
2. Scribe line width: X=80µm, Y=80µm
3. Pad size: 100µm x 100µm
4. Substrate to GND
Figure 1. 8~450V Powered Driver for Two
White Power LEDs
5. Wafer thickness: 460µm
P.2
PJ9910
WIDE INPUT RANGE
POWER LED DRIVER
PAD LOCATION
μ
X ( m)
μ
Y ( m)
Pad
1
Pad Name
VIN
CS
-887.5
0
110
0
2
3
GND
GND
GATE
PWM_D
VDD
255.5
395.5
587.0
556.5
375.5
235.5
-1012.5
-1012.5
0
4
0
5
544.5
1259.5
1290
1290
1260.5
1044.5
6
7
8
VDD
9
LD
10
ROSC
DIE PHOTO
P.3
PJ9910
WIDE INPUT RANGE
POWER LED DRIVER
℃
ELECTRICAL CHARACTERISTICS (TA=25 , unless otherwise noted.
Symbol
Description
Min Typ Max Unit Condition
VINDC Input DC supply voltage range
8.0
7.0
450
1
V
DC input voltage
IINsd
Shut-Down mode supply current
0.5
7.5
mA
Pin PWM_D to
GND, VIN=8V
VDD
Internally regulated voltage
8.0
V
V
VIN=8-450V,
I
DD(ext)=0, pin Gate
open
VDDmax Maximal pin VDD voltage
13.5
When an external
voltage applied to
pin VDD
IDD(ext) VDD current available for external
circuitry
1.0
mA
VIN=8-100V
UVLO VDD undervoltage lockout threshold
6.45
6.7
6.95
V
mV
V
VIN rising
VIN falling
VIN=8-450V
VIN=8-450V
VEN=5V
Δ
UVLO
VDD undervoltage lockout hysteresis
500
VEN(lo) Pin PWM_D input low voltage
VEN(hi) Pin PWM_D input high voltage
RLN Pin PWM_D pull-down resistance
1.0
2.4
50
V
Ω
k
100
250
150
275
℃
TA=-40
to
VCS(hi) Current sense pull-in threshold voltage 225
mV
℃
+85
VGATE(hi) GATE high output voltage
VDD-
0.3
VDD
V
IOUT=-10mA
VGATE(lo) GATE low output voltage
0
0.3
30
V
IOUT=10mA
ROSC=1.00M
Ω
fosc
Oscillator frequency
20
80
25
kHz
kHz
%
Ω
ROSC=223k
100
120
100
DmaxHT Maximum Oscillator PWM duty cycle
FPWMhf=25kHz, at
GATE, CS to GND
℃
TA=<85
VIN=12V
,
VLD
Linear Dimming pin voltage range
0
250
mV
P.4
PJ9910
WIDE INPUT RANGE
POWER LED DRIVER
TBLANK Current sense blanking interval
tDELAY Delay from CS trip to GATE lo
150
215
280
ns
VCS=0.55VLD,
VLD=VDD
300
ns
VIN=12V,
VLD=0.15V, VCS=0
to 0.22V after
TBLANK
tRISE
GATE output rise time
30
30
50
50
ns
ns
CGATE=500pF, 10%
to 90% VGATE
tFALL GATE output fall time
CGATE=500pF, 90%
to 10% VGATE
Note: Also limited by package power dissipation limit, whichever is lower.
8 SOIC PACKAGE
PIN DESCRIPTION
Application Note
Buck-based LED Drivers
Fundamental Buck Converter topology is an
excellent choice for LED drivers in off-line (as
well as low-voltage) applications as it can
produce a constant LED current at very high
efficiencies and low cost. A
The low sense voltage allows the use of low
current sense resistor values. IC PJ9910C operates
down to 8V input, which is required for some low
input voltage applications, and can take a
maximum of 450V input, which makes it ideal for
peak-current-controlled buck converter can give off-line applications. It also has an internal
reasonable LED current variation over a wide regulator that supplies power to the IC from the
range of input and LED voltages and needs little input voltage, eliminating the need for an external
effort in feedback control design. Coupled with
the fact that these converters can be easily
low voltage power supply. It is capable of driving
the external FET directly, without the need for
designed to operate at above 90% efficiency, the additional driver circuitry. Linear or PWM dimming
buck-based driver becomes an unbeatable
solution to drive High Brightness LEDs.
can also be easily implemented using the IC
PJ9910C.
The IC PJ9910C provides a low-cost, low
This Application Note discusses the design of a
component count solution to implement the
buck-based LED driver using the IC PJ9910C with
continuous mode buck converter. IC PJ9910C has the help of an off-line application example. The
two current sense threshold voltages – an
internally set 250mV and an external voltage at
the LD pin. The actual threshold voltage will be
the lower of the internal 250mV and the voltage
at the LD pin.
same procedure can be used to design LED
drivers with any other lower voltage AC or DC
input; 12V for example.
Circuit Diagram
loss dissipation during normal operation of the
Step1: Switching Frequency and resistor (R1)
The switching frequency determines the size of the converter, and must be minimized. A good rule of
inductor L1 and size or type of input filter capacitor thumb is that the thermistor should limit the inrush
C1. A larger switching frequency will result in a
smaller inductor, but will increase the switching
current to not more than five times the steady state
current as given by equation (2), assuming
losses in the circuit. For off-line applications, typical maximum voltage is applied. The required cold
switching frequencies should be in range
resistance is:
20-150kHz. The higher the input voltage range (for
example in Europe 230VAC), the lower the
frequency should be to avoid extensive capacitive
losses in the converter. For North America AC line
a frequency of fs=100kHz is a good compromise.
This gives us a 200Ω resistance at 25℃. Choose
a thermistor with a resistance around 200Ω and
From the datasheet, the oscillator resistor needed rms current greater than 0.2A for that application.
to achieve this is 228kΩ.
Step3: Choose the Input Capacitors (C1 and C2)
The first design criterion to meet is that the
Step2: Choose the Input Diode Bridge (D1)
The voltage rating of the diode bridge will depend maximum LED string voltage should be less than
on the maximum value of the input voltage. The
half the minimum input voltage to avoid having to
current rating will depend on the maximum average implement a special loop compensation technique.
current drawn by the converter.
For this example, the minimum rectified voltage
should be:
The hold-up and input filter capacitor required at
The 1.5 factor in equation (1) a 50% safety margin the diode bridge output have to be calculated at the
is more than enough. For this design, choose a
400V, 1A diode bridge.
minimum AC input voltage. The minimum capacitor
value can be calculated as:
Placing a thermistor (or resistor) in series with input
bridge rectifier will effectively limit the inrush
current to input bulk capacitor C1 during the initial
start-up of the converter. Except this useful action
during very short time interval, such a series
element creates a unnecessary power
In this example, C1≧ 26.45μF.
Note: Equation (5) yields a conservative estimate lifetime. Then, the inductor L1 can be computed at
to for the least amount of capacitance required. It rectified value of the nominal input voltage as:
means that the capacitor filter will normally care
large ripple content. Some electrolytic capacitors
may not be able to withstand such ripple current
and minimum value of C1 capacitor may not be
met, forcing the design to use larger value
capacitor. In the case where the allowable ripple at
the input of the buck converter is large, the
In this example, L1 = 2.9mH
capacitor C1 can be reduced significantly. See the The peak current rating of the inductor will be:
Appendix for a more accurate calculation of the
required capacitor value.
The voltage rating of the capacitor should be more The rms current through the inductor will be the
than the peak input voltage with 10-12% safety
margin.
same as the average current for the chosen 30%
ripple.
Right inductor for this application is an off-the-shelf
2.7mH, 0.54A(peak), 0.33A(rms) inductor.
Choose a 250V, 33μF electrolyte capacitor.
Step5: Choose the FET (Q1) and Diode (D2)
The peak voltage seen by the FET is equal to the
maximum input voltage. Using a 50% safety rating,
Such electrolytic capacitors have a sizable ESR
component. The larger ESR of these capacitors
makes it inappropriate to absorb the high
frequency ripple current generated by the buck
converter. Thus, adding a small MLCC capacitor in The maximum rms current through the FET
parallel with the electrolytic capacitor is a good depends on the maximum duty cycle, which is 50%
option to absorb the high frequency ripple current. by design. Hence, the current rating of the FET is:
The required high frequency capacitance can be
computed as:
Typically a FET with about 3 times the current is
chosen to minimize the resistive losses in the
In this design example, the high frequency
switch.
capacitance required is about 250V, 22μF.
For this application choose a 300V, <1A MOSFET,
such as a BSP130 from Philips. Actual MOSFET
type should be determined by the transistor
Step4: Choose the Inductor (L1)
The inductor value depends on the ripple current in permitted power dissipation on printed board. For
the LEDs. Assume a +/- 15% ripple (a total of 30%) example, a BSP130 SOT-223 package limits the
in the LED current, an aggressive assumption
would go up to +/- 30% to reduce the size of the
inductor more than twice at the price of reduced
efficiency and , possibly, reduced LED
dissipation to less than a Watt at 50+ Celsius, even
if the MOSFET peak current capability is 1.5A. A
good rule of thumb is to limit overall MOSFET
power dissipation to not more than 3-5% of total
Design for DC/DC Applications
output power, by making a right transistor choice.
In choosing MOSFET transistors for such LED
The same procedure can be used for DC/DC
drivers, going bigger does not mean getting better, applications. The only modifications are that the
just the opposite. Using TO-220 transistor
500/4A/2W instead of SOT-223 transistor
300V/0.5A/6W does not more harm than good,
reducing overall efficiency by several percent.
input diode bridge and input hold-up capacitor are
not required. A small input capacitance to absorb
high frequency ripple current is all that is required.
The capacitance can be computed using
equation(7).
The peak voltage rating of the diode is the same as
the FET. Hence,
Appendix
The more accurate equations for computing the
required capacitance values are:
The average current through the diode is:
Choose a 300V, 1A ultra-fast diode.
Step6: Choose the Sense Resistor (R2)
The sense resistor value is given by:
For the example in this application note, the actual
minimum capacitance required from the above
equations is 19μF (as compared to 26μF from
equation(5)).
if the internal voltage threshold is being used.
Otherwise, substitute the voltage at the LD pin
instead of the 0.25V in equation(14).
For this design, R2= 0.55Ω. Also calculate the
resistor power dissipation:
A 0.1W resistor is good for this application.
Note: Capacitor C3 is a bypass capacitor. A typical
value of 1.0 to 2.2μF, 16V is recommended.
1
2
3
4
D
C
B
A
D
C
B
A
L1
P1
FUSE1
1R/1W
LED+
3mH
C12
L2
15mH
C1
RT1
275VAC
AC
102
10uF/250V
1000V
D8
R3
BD1
MB6S
D7
M7
LED
LED
C10
C5
0.1uF/275VA
SF26
1M
RV1
275VAC
102
T1
15mH
1000V
C11
...
102
P2
D6
M7
1000V
D5
M7
DZ2
12V
C3
C9
102
AC
22uF/50V
Vin=110/220VAC
LED-
25
C2
10uF/250V
Q1
串
4
并
I=240ma
PJ2N60
D9
SS14
R4
2K
U1 PJ9910S
1
2
3
4
8
7
6
5
VSS VDD
C7
EN
NC
TOFF
CS
470pF
Q2
DZ1
5.1V
PJM3400
GND DRV
C4
C8
104
22uF/50V
R6
82K
R5
3R 1%
R7
R8
R9
3 R 1%
3 R 1%
3R 1%
VR1
100R
C6
2pF
项目1驱动电路.Sch
1
2
3
4
PJ9910S PCBA BOM
Part
Number
Ref Unit
Price(RMB)
Part Type
PCB
DESCRIPTION
Footprint
N/A
Ref
PCB
Quantity Unit
1
PJ9910S驱动电路板 V0.0.PCB,236mm x 20mm x 1.2mm FR-4
1
PCS
3.00
2
3
4
5
6
7
8
9
10
11
12
13
14
15
16
IC
PJ9910S,LED Driver IC
MB6S,600V 500mA
PJ2N60,600V 2A
PJM3400,30V 5A
1N4007(M7),1000V 1A
SF26,400V 2A
SS14(1N5819),40V 1A
C12V,12V 1/2W
C5V1,5.1V 1/2W
1 ohm,1W
1M ohm,1/8W
1.2K ohm,1/8W
3 ohm,1/8W
1 ohm,1/8W
82K ohm,1/8W
SOP8
SOIC-4
TO-252
SOT-23
DO-214AC
D0-15
DO-214AC
MLL34
SOD-123
AXIAL-0.5
0805
U1
BD1
Q1
1
1
1
1
3
1
1
1
1
1
1
1
2
1
1
1
2
1
1
2
1
1
2
1
1
1
1
PCS
PCS
PCS
PCS
PCS
PCS
PCS
PCS
PCS
PCS
PCS
PCS
PCS
PCS
PCS
PCS
PCS
PCS
PCS
PCS
PCS
PCS
PCS
PCS
PCS
PCS
PCS
3.80
1.00
2.00
0.60
0.40
0.50
0.20
0.15
0.15
0.15
0.02
0.02
0.02
0.02
0.02
0.60
0.90
0.30
0.30
0.35
0.02
0.02
0.02
1.50
0.90
0.05
0.50
Bridge
MOSFET
MOSFET
Doide
Doide
Doide
Q2
D5 D6 D7
D8
D9
DZ2
DZ1
FUSE1
R3
Zenor
Zenor
Resistor
Resistor
Resistor
Resistor
Resistor
Resistor
0805
0805
0805
0805
R4
R5 R9
R8
R6
17 Variable Resistor
100 ohm,Variable Resistor
10uF/250V ,E-cap
1uF/50V,E-cap
VR-5
VR
18
19
20
21
22
23
24
Capacitor
Capacitor
Capacitor
Capacitor
Capacitor
Capacitor
Capacitor
CD110
CD11
CD11
RAD-0.4
0805
0805
C1 C2
C3
C4
C5 C10
C6
C7
C8 C9
T1
L1
L2
RV1
47uF/16V,E-cap
0.1uF/275VAC,MKX/MKP X2
2pF, Ceramic Capacitor
470pF, Ceramic Capacitor
0.1uF, Ceramic Capacitor
20mH/800mA,10x6x5
2.5mH/1000mA,10x16
Line ,L=8.5mm,d=0.5mm
5D471，470V，D=5mm
0805
25 Common Coil
10x16
10x16
N/A
26
27
28
Inductor
Line
RV
RAD-0.2
29
RT
Line ,L=5.0mm,d=0.5mm
N/A
L2
1
PCS
0.05
Total:
35
17.56
First release
REV:0.0
Vendor info
Vendor contact info
0755-83674428
PJ
PJ
0755-83674428
Fairchild Semiconductor
N/A
PJ
0755-83674428
PJ
0755-83674428
N/A
N/A
Phiphs
Leshan Radio Company
YueJing Hi-tech Company
Leshan Radio Company
YueJing Hi-tech Company
N/A
N/A
N/A
N/A
N/A
N/A
N/A
N/A
N/A
N/A
N/A
N/A
Fenghua Advanced Technology (holding) Co., Ltd
Fenghua Advanced Technology (holding) Co., Ltd
Fenghua Advanced Technology (holding) Co., Ltd
Fenghua Advanced Technology (holding) Co., Ltd
Fenghua Advanced Technology (holding) Co., Ltd
Fenghua Advanced Technology (holding) Co., Ltd
Fenghua Advanced Technology (holding) Co., Ltd
Rubycon
Rubycon
Rubycon
N/A
N/A
N/A
N/A
N/A
N/A
SHENZHEN SURONG CAPACITORS CO.，LTD
Fenghua Advanced Technology (holding) Co., Ltd
Fenghua Advanced Technology (holding) Co., Ltd
Fenghua Advanced Technology (holding) Co., Ltd
Miden Electronics Ltd.
Miden Electronics Ltd.
N/A
N/A
N/A
WEI DE CHANG Elect Ltd.
N/A
N/A
N/A
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