STEL-1177/CM [ETC]
Numeric-Controlled Oscillator ; 数字控制振荡器\n型号: | STEL-1177/CM |
厂家: | ETC |
描述: | Numeric-Controlled Oscillator
|
文件: | 总17页 (文件大小:268K) |
中文: | 中文翻译 | 下载: | 下载PDF数据表文档文件 |
STEL-1177
Data Sheet
STEL-1177
32-Bit Resolution
CMOS Phase and
Frequency Modulated
Numerically
Controlled Oscillator
R
Powered by ICminer.com Electronic-Library Service CopyRight 2003
F E A T U R E S
■ HIGH CLOCK FREQUENCY
■ HIGH SPECTRAL PURITY
- 60 MHz MAXIMUM OVER COMMERCIAL
- ALL SPURS < –75 dBc
TEMPERATURE
40 MHz MAXIMUM OVER FULL MILITARY
TEMPERATURE RANGE
■ HIGH FREQUENCY RESOLUTION
RANGE
■ MICROPROCESSOR
COMPATIBLE
-
I N P U T S
■ LOW POWER DISSIPATION
- COSINE CHANNEL CAN BE DISABLED
TO REDUCE POWER
- 32-BITS, 14 milli-Hz @ 60 MHz
■ WIDE OUTPUT BANDWIDTH
■ 84 PIN PLCC OR CLDCC PACKAGES
AND 84 PIN CERAMIC PGA PACKAGE
A V A I L A B L E
- 0 TO 25 MHz @ 60 MHz CLOCK
■ PRECISION
PHASE
MODULATION
- 12-BITS, 0.09° RESOLUTION, CAN BE
USED FOR LINEAR PM OR PULSE-
SHAPED PSK
TYPICAL
APPLICATIONS
■ PRECISION
FREQUENCY
MODULATION
■ FREQUENCY
SYNTHESIZERS
- 16 BITS RESOLUTION, CAN BE USED
FOR LINEAR FM OR PULSE-SHAPED FSK
■ FSK AND PSK MODULATORS
■ DIGITAL SIGNAL PROCESSORS
■ QUADRATURE
SIGNAL
GENERATION
- 12-BIT OUTPUTS WITH INDEPENDENT
PHASE MODULATION PER CHANNEL
■ HIGH SPEED HOPPED FREQUENCY
SOURCES
BLOCK
DIAGRAM
PHLD
ROUND
CLOCK
CIN
4
ADDR
CSEL
SYNC
FMSYNC
ADDRESS
SELECT
LOGIC
WRSTB
SINE
PHASE
MOD
PHSEL
DATA
8
12
CONTROL
COSINE
PHASE
MOD
32
13
SINE
PHASE
ALU
13
12
SINE
LUT
SINE
12
32
CONTROL
-PHASE
BUFFER
REGISTER
A
-PHASE
ALU
ALU
BUFFER
REGISTER
PHASE
ACCUM-
ULATOR
MUX
-PHASE
BUFFER
REGISTER
B
32
RESET
FRSEL
(TO ALL REGISTERS)
FRE-
QUENCY
MOD
COSINE
LUT
COSINE
PHASE
ALU
12
13
13
FMSUB
FMLD
COSINE
CONTROL
SIMLD
FMOD
16
2
RATE
2
FMADDR
FRLD
COSEN
STEL-1177
2
Powered by ICminer.com Electronic-Library Service CopyRight 2003
PIN
CONFIGURATION
1. Plastic (PLCC) (/CM) or Ceramic (CLDCC) (/CC and /MC) Leaded Chip Carrier
Package:
Package:
84 pin CLDCC
84 pin PLCC
Thermal coefficient, qja = 34°/W
Thermal coefficient, qja = 30°/W
0.145"
max.
1
1
8
8 8 8 8 7 7 7 7
7
5
1
1
1
0
8
4
8
3
8
2
8
1
8
0
7
9
7
8
7
7
7
6
7
5
1 0 9 8 7 6 5 4 3 2 1 4 3 2 1 0 9 8 7 6
9
8
7
6
5
4
3 2 1
74
73
72
71
70
69
68
67
66
65
64
63
62
61
60
59
58
57
56
55
54
12
13
14
15
16
17
18
19
20
21
22
23
24
25
26
27
28
29
30
31
32
12
13
14
15
16
17
18
19
20
21
22
23
24
25
26
27
28
29
30
31
32
74
0.017"
± 0.004" (2)
0.018"
± 0.004" (2)
1.190"
± 0.005"
Top View
Top View
0.05"
nominal (1)
0.05"
± 0.005" (1)
3
3
3
4
3
5
3
6
3
7
3
8
3
9
4
0
4
1
4
2
4
3
4
4
4
5
4
6
4
7
4
8
4
9
5
0
5
1
5
2
5
3
3 3 3 3 3 3 3 4 4 4 4 4 4 4 4 4 4 5 5 5 5
3 4 5 6 7 8 9 0 1 2 3 4 5 6 7 8 9 0 1 2 3
0.035"
nominal
0.200"
max.
1.154"
± 0.004"
1.150"
± 0.012"
Notes:
1. Dimensions shown are for plastic package.
Dimensions for ceramic package are similar.
2. Tolerances on pin spacing are not cumulative.
2. Ceramic Pin Grid Array (CPGA) (/CF and /MF)
1 2 3 4 5 6 7 8 9 1011
L
K
J
H
G
F
0.1"
± .005"
0.117"
max.
0.18"
± .005"
E
D
C
B
A
0.018"
± .001" dia.
1.10" ± .02 "sq..
Notes: 1. Tolerances on pin spacings are not
cumulative.
2. Corner pins have integral standoffs
which raise the package 0.07" (nominal)
above the mounting surface.
3. Orientation determined by extra pin at
location C3.
4. Thermal coefficient, θja = 28°C/watt
3
STEL-1177
Powered by ICminer.com Electronic-Library Service CopyRight 2003
PIN
CONNECTIONS
1
2
3
4
5
6
7
8
9
(C6) VSS
22 (F3) VSS
43 (J6)
44 (J7)
VSS
COS4
64 (F9) VSS
(A6) FMOD7
(A5) FMOD8
(B5) FMOD9
(C5) FMOD10
(A4) FMOD11
(B4) FMOD12
(A3) FMOD13
(A2) FMOD14
23 (G3) CLOCK
24 (G1) SIMLD
25 (G2) ADDR3
26 (F1) ADDR2
27 (H1) ADDR1
28 (H2) ADDR0
65 (F11) SINE10
66 (E11) SINE11
67 (E10) RATE0
68 (E9) RATE1
69 (D11) ROUND
70 (D10) COSEN
71 (C11) VSS
72 (B11) FMLD
73 (C10) FMSYNC
74 (A11) VDD
75 (B10) FMSUB
76 (B9) FMADDR0
77 (A10) FMADDR1
78 (A9) FMOD0
79 (B8) FMOD1
80 (A8) FMOD2
81 (B6) FMOD3
82 (B7) FMOD4
83 (A7) FMOD5
45 (L7) COS5
46 (K7) COS6
47 (L6) COS7
48 (L8) COS8
49 (K8) COS9
50 (L9) COS10
51 (L10) COS11
52 (K9) VSS
29 (J1)
30 (K1) FRSEL
31 (J2) VSS
CSEL
10 (B3) FMOD15
11 (A1) VDD
32 (L1) VDD
33 (K2) PHLD
34 (K3) PHSEL
35 (L2) CIN
36 (L3) FRLD
37 (K4) SYNC
38 (L4) I.C.
53 (L11) VDD
12 (B2) DATA7
13 (C2) DATA6
14 (B1) DATA5
15 (C1) DATA4
16 (D2) DATA3
17 (D1) DATA2
18 (E3) DATA1
19 (E2) DATA0
20 (E1) WRSTB
21 (F2) RESET
54 (K10) SINE0(LSB)
55 (J10) SINE1
56 (K11) SINE2
57 (J11) SINE3
58 (H10) SINE4
59 (H11) SINE5
60 (F10) SINE6
61 (G10) SINE7
62 (G11) SINE8
63 (G9) SINE9
39 (J5)
COS0(LSB)
40 (K5) COS1
41 (L5) COS2
42 (K6) COS3
84 (C7
FMOD6
Numeric pin connections are for PLCC and CLDCC packages, alphanumeric connections in parentheses are for
PGA package. Note: I.C. denotes Internal Connection. These pins must be left unconnected. Do not use for vias.
FUNCTIONAL
DESCRIPTION
number in the ∆-Phase register represents the phase
change for each cycle of the clock. This number is
directly related to the output frequency by the
following:
The STEL-1177 Modulated Numerically Controlled
Oscillator (MNCO) uses digital techniques to provide
a cost-effective solution for low noise signal sources.
The NCO features high frequency resolution with
exceptional spectral purity of outputs up to 25 MHz.
The STEL-1177 also features both phase and frequency
modulation at rates up to 25% of the clock frequency.
Separate 12-bit sine and cosine outputs are provided
which can be phase modulated independently. The
cosine channel can be disabled when not in use,
reducing the power consumption by approximately
30%. The device combines low power 1.5µ CMOS
technology with a unique architectural design
resulting in a power efficient, high-speed sinusoidal
waveform generator able to achieve fine tuning
resolution and exceptional spectral purity at clock
frequencies up to 60 MHz. The NCO is designed to
provide a simple interface to an 8-bit microprocessor
bus.
fc x ∆-Phase
fo=
232
where: fo is the frequency of the output signal
and: fc is the clock frequency.
The sine and cosine functions are generated from the
13 most significant bits of the phase accumulator. The
frequency of the NCO is determined by the number
stored in the ∆-Phase Register, which may be
programmed by an 8-bit microprocessor, and the
frequency modulation value loaded on the FMOD
bus. The carrier frequency and the frequency
modulation can be updated independently or
simultaneously, using an internal synchronization
circuit which ensures glitch-free updates.
The NCO maintains a record of phase which is
accurate to 32 bits. At each clock cycle, the number
stored in the 32-bit ∆-Phase register is added to the
previous value of the phase accumulator. The number
in the phase accumulator represents the current phase
of the synthesized sine and cosine functions. The
The NCO generates a sampled sine wave where the
sampling function is the clock. The practical upper
limit of the NCO output frequency is about 40% of the
clock frequency due to spurious components that are
created by sampling. Those components are at
STEL-1177
4
Powered by ICminer.com Electronic-Library Service CopyRight 2003
frequencies greater than half the clock frequency, and
become more difficult to remove by filtering as the
output frequency approaches half the clock frequency.
different phase modulation can be applied to the sine
and cosine channels.
∆-PHASE BUFFER REGISTERS A & B BLOCK
The two ∆-Phase Buffer Registers are used to
The phase noise of the NCO output signal may be
determined from the phase noise of the clock signal
input and the ratio of the output frequency to the clock
frequency. This ratio squared times the phase noise
power of the clock specified in a given bandwidth is
the phase noise power that may be expected in that
same bandwidth relative to the output frequency.
temporarily store the ∆-Phase data written into the
device. This allows the data to be written
asynchronously as four bytes per 32-bit ∆-Phase word.
The data is transferred from these registers into the ∆-
Phase ALU after a falling edge on the FRLD input.
MUX BLOCK
The NCO achieves its high operating frequency by
making extensive use of pipelining in its architecture.
The pipeline delays within the NCO represent 19 clock
cycles. The dual ∆-Phase registers used in the STEL-
1177 allow the frequency and frequency modulation to
be updated as rapidly as every fourth clock cycle, i.e. at
25% of the clock frequency. The pipeline delay
associated with the phase modulator is only 12 clock
cycles, since the phase modulating function is at the
output of the accumulator. The phase modulation may
also be changed as rapidly as every fourth clock cycle,
at 25% of the clock frequency, resulting in a maximum
modulation rate of 15 MHz with a clock frequency of
60 MHz. Note that when a phase or frequency change
occurs at the output the change is instantaneous, i.e., it
occurs in one clock cycle, with complete phase
coherence.
This block is used to select which ∆-Phase Buffer
Register is used as the source of frequency data for the
∆-Phase ALU, by means of the FRSEL input.
FREQUENCY
B L O C K
MODULATION
CONTROL
This block controls the writing of the frequency
modulation (FM) data on the FMOD15-0 bus into the
FM Buffer Register, and the loading of this data into
the ∆-Phase ALU. This data is multiplied by a factor of
20, 24, 28, or 212, according to the state of the
FMADDR1-0 inputs, before being loaded into the ∆-
Phase ALU. This gives a wide range of values for the
maximum deviation and resolution. The writing of the
FM data can be either manual or automatic. It is
controlled by the RATE1-0 inputs, and the FMLD
input or the FMSYNC output, depending on the mode
selected. In addition, this block synchronizes the
simultaneous updating of the carrier frequency data
and FM data when the SIMLD input is high.
FUNCTION
BLOCK
DESCRIPTION
ADDRESS SELECT LOGIC BLOCK
∆-PHASE ALU BLOCK
This block controls the writing of data into the device
This block controls the updating of the ∆-Phase word
via the DATA7-0 inputs. The data is written into the
device on the rising edge of the WRSTB input, and the
register into which the data is written is selected by the
ADDR3-0 inputs. The CSEL input can be used to
selectively enable the writing of data from the bus.
used in the Accumulator. The frequency data from the
Mux Block is loaded into this block after a falling edge
on the FRLD input, and the FM data from the
Frequency Modulation Control block is loaded after a
falling edge on the FMLD input. However, if the
SIMLD input is high, the FMLD input will load both
sets of data simultaneously. The FM data is added to
or subtracted from the carrier frequency data, the
add/subtract operation being selected by the FMSUB
input. This block also generates the SYNC output,
which indicates the instant at which any phase or
frequency change made at the inputs affects the
SINE11-0 and COS11-0 output signals, and also the
FMSYNC output, which controls the loading of the
FM data on the FMOD15-0 bus in the automatic mode.
SIN/COS PHASE MODULATION BLOCK
This block includes the Phase Modulation Buffer
Registers, and controls the source of the phase
modulation (PM) data by means of the PHSEL input.
When this signal is low, data from the DATA7-0 and
ADDR3-0 inputs is written directly into the Phase ALUs
after a falling edge on the PHLD input. The same PM
data will be applied to both the Sine and Cosine Phase
ALUs in this mode. When PHSEL is high, data is
written into the Phase Modulation Buffer Registers
from the DATA7-0 bus on the rising edge of the WRSTB
input. The data will then be transferred into the Sine
and Cosine ALUs after the next falling edge of PHLD.
The sources of the PM data applied to the Sine and
Cosine Phase ALUs will be the independent Sine and
Cosine Phase Buffer Registers in this mode, so that
ALU BUFFER REGISTER BLOCK
This block stores the output from the ∆-Phase ALU for
use in the Phase Accumulator. It also controls the time
alignment of this data whenever it is changed, so that
glitch-free updating of the accumulator pipeline is
achieved.
5
STEL-1177
Powered by ICminer.com Electronic-Library Service CopyRight 2003
PHASE ACCUMULATOR BLOCK
This block forms the core of the NCO function. It is a
DATA7 through DATA0
The 8-bit DATA7-0 bus is used to program the two 32-
high-speed, pipelined, 32-bit parallel accumulator,
generating a new sum in every clock cycle. A carry
input (the CIN input) allows the resolution of the
accumulator to be expanded by means of an auxiliary
NCO or phase accumulator. The overflow signal is
discarded, since the required output is the
modulo(232) sum only. This represents the modulo(2π)
phase angle.
bit ∆-Phase Registers and the two 12-bit Phase
Modulation Registers. DATA0 is the least significant
bit of the bus. The data programmed into the ∆-Phase
registers in this way determines the carrier frequency
of the NCO.
ADDR3 through ADDR0
The four address lines ADDR3-0 control the use of the
DATA7-0 bus for writing frequency data to the ∆-
Phase Buffer Registers, and phase data to the Phase
Buffer Registers, as shown in the table:
PHASE ALU BLOCKS
The two Phase ALUs perform the addition of the sine
and cosine PM data to the Phase Accumulator output
in the sine and cosine channels, respectively. The PM
data words are both 12 bits wide, and these are added
to the 13 most significant bits from the Phase
Accumulator to form the modulated phase used to
address the lookup tables.
ADDR3 ADDR1 ADDR0 Register Field
0
0
0
0
1
1
1
1
0
0
1
1
0
0
1
1
0
1
0
1
0
1
0
1
∆-Phase Bits 0 (LSB)–7
∆-Phase Bits 8–15
∆-Phase Bits 16–23
∆-Phase Bits 24–31
Sine Bits 0(LSB)–3*
Sine Bits 4-11*
SINE AND COSINE LOOKUP TABLE BLOCKS
These blocks are the sine and cosine memories. The 13
bits from the Phase ALUs are used to address these
memories to generate the 12-bit SINE11-0 and COS11-0
outputs. The Cosine LUT can be disabled when not in
use, to conserve power, by means of the COSEN
input.
Cosine Bits 0(LSB)–3*
Cosine Bits 4-11*
ADDR3 ADDR2
Register Selected
INPUT
SIGNALS
0
0
1
0
1
∆-Phase Buffer Register 'A'
∆-Phase Buffer Register 'B'
Phase Buffer Registers
R E S E T
The RESET input is asynchronous and active low, and
clears all the registers in the device. When RESET goes
low, all registers are cleared within 20 nsecs, and
normal operation will resume after this signal returns
high. The data on the SINE11-0 and COS11-0 buses will
then be invalid for 7 clock cycles, and thereafter will
remain at the value corresponding to zero phase until
new frequency or modulation (either frequency or
phase) data is loaded with the FRLD, FMLD, or
PHLD inputs after the RESET returns high.
X
* Note: The Phase Buffer Registers are 12-bit registers.
When the least significant bytes of these registers are
selected (ADDR3-0 =1XX0), DATA7-4 is written into
Bits 3–0 of the registers. In all cases, it is not necessary
to reload unchanged bytes, and the byte loading
sequence may be random.
W R S T B
The Write Strobe input is used to latch the data on the
C L O C K
DATA7-0 bus into the device. On the rising edge of the
WRSTB input, the information on the 8-bit data bus is
transferred to the buffer register selected by the
ADDR3-0 bus.
All synchronous functions performed within the NCO
are referenced to the rising edge of the CLOCK input.
The CLOCK signal should be nominally a square
wave at a maximum frequency of 60 MHz. A non-
repetitive CLOCK waveform is permissible as long as
the minimum duration positive or negative pulse on
the waveform is always greater than 5 nanoseconds.
F R S E L
The Frequency Register Select line is used to control
the mux which selects the ∆-Phase Buffer Register in
use. When this signal is high ∆-Phase Buffer Register
'A' is selected as the source for the ∆-Phase ALU, and
the frequency corresponding to the data stored in this
register will be generated by the NCO after the next
falling edge on the FRLD input. When this line is low,
∆-Phase Buffer Register 'B' is selected as the source.
C S E L
The Chip Select input is used to control the writing of
data into the chip. It is active low. When this input is
high all data writing via the DATA7-0 bus is inhibited.
STEL-1177
6
Powered by ICminer.com Electronic-Library Service CopyRight 2003
F R L D
FMADDR1 through FMADDR0
The two inputs FMADDR1-0 set the deviation of the
The Frequency Load input is used to control the
transfer of the data from the ∆-Phase Buffer Registers
to the ∆-Phase ALU. The data at the output of the Mux
Block must be valid during the clock cycle following
the falling edge of FRLD. The data is then transferred
during the subsequent cycle. The frequency of the
NCO output will change 19 clock cycles after the
FRLD command due to pipelining delays.
frequency modulation by controlling the significance
of the FM data in relation to the carrier frequency data.
The FM data word will be multiplied by 20, 24, 28, or
212 according to the state of FMADDR1-0, and the
consequent resolution and maximum values of the
deviation are shown in the table below. The values
shown are for a clock frequency of 60 MHz.
P H S E L
FM-
FM- Mult. factor Maximum Resol-
The Phase Source Select input selects the sources of
ADDR1 ADDR0 of FM data deviation
ution
data for the Phase ALUs. When it is high the sources
are the Sine and Cosine Phase Buffer Registers. They
are loaded from the DATA7-0 bus by setting address
line ADDR3 high, as shown in the tables. When
PHSEL is low, the sources for the phase modulation
data are the DATA7-0 and ADDR3-0 inputs, and the
data will be loaded independently of the states of
WRSTB and CSEL. The data on these 12 lines is
presented directly as a parallel 12-bit word to both
Phase ALUs, allowing high-speed phase modulation.
The 12-bit value is latched into the Phase ALUs by
means of the PHLD input. The data on the ADDR3-0
lines is mapped onto Phase Bits 3 to 0 and the data on
the DATA7-0 lines are mapped onto Phase Bits 11 to 4
in this case. When using the parallel phase load mode
CSEL and/or WRSTB should remain high to ensure
that the phase data is not written into the phase and
frequency buffer registers of the STEL-1177.
0
0
1
1
0
1
0
1
20
24
28
212
± 915 Hz
14 mHz
± 14.6 KHz 0.22 Hz
± 234 KHz 3.6 Hz
± 3.75 MHz 57 Hz
F M L D
The FM Load input controls the writing of the
frequency modulation data on the FMOD15-0 bus and
the FMSUB input into the device. When RATE1-0= 00
the data at the output of the Frequency Modulation
Control Block must be valid during the clock cycle
following the falling edge of FMLD. The data is then
transferred during the subsequent cycle. When
RATE1-0= 01, 10 or 11 are selected the FM data will be
loaded automatically without the use of the FMLD
input. Note that FMLD must be held low during
automatic operation, otherwise the loading will be
inhibited.
P H L D
The Phase Load input is used to control the latching of
the Phase Modulation data into the Phase ALUs. The
12-bit data at the output of the Phase Modulation
Control Block must be valid during the clock cycle
following the falling edge of PHLD. The data is then
transferred during the subsequent cycle. The 12-bit
phase data is added to the 12 most significant bits of
the accumulator output, so that the MSB of the phase
data represents a 180° phase change. The source of this
data will be determined by the state of PHSEL. The
phase of the NCO output will change 12 clock cycles
after the PHLD command, due to pipelining delays.
S I M L D
The Simultaneous Load input allows the carrier
frequency data from the Mux Block and the FM data
to be updated simultaneously. When SIMLD is low,
only the FM data will be updated after a falling edge
on FMLD. When this input is high, both the FM data
and carrier frequency data will be updated
simultaneously. When SIMLD is low at least four
clock cycles are required between falling edges of
FMLD and FRLD to ensure glitch-free changes in the
outputs.
FMOD15 through FMOD0
The Frequency Modulation bus is a 16-bit bus on
which the FM data is loaded into the STEL-1177. The
data should be a 16-bit unsigned number.
R A T E1 - 0
The RATE1-0 signals control the rate at which the FM
data on the FMOD15-0 bus is added to or subtracted
from the carrier frequency, as shown in the table
below:
F M S U B
The FM Subtract input controls the Add/Subtract
operation of the ∆-Phase ALU. When it is high the FM
data on the FMOD15-0 bus will be subtracted from the
carrier frequency, and when it is low the FM data will
be added to the carrier frequency. In this way the FM
data can be treated as a 17-bit signed-magnitude
number, where the FMSUB signal is the sign bit.
RATE1 RATE0
Modulation Update Rate
0
0
1
1
0
1
0
1
Manual, with FMLD signal
Every 4th clock cycle
Every 8th clock cycle
Every 16th clock cycle
FMSUB is latched at the same time as FMOD15-0
.
7
STEL-1177
Powered by ICminer.com Electronic-Library Service CopyRight 2003
COS11-0
C I N
The signal appearing on the COS11-0 outputs is
The Carry Input is an arithmetic carry to the least
derived from the 13 most significant bits of the Phase
Accumulator. The 12-bit cosine function is presented
in offset binary format. When the phase accumulator
is zero, e.g., after a reset, the decimal value of the
output is 4095 (FFFH). When the phase modulation is
zero the value of the output for a given phase value
follows the relationship:
significant bit of the Accumulator. Normal operation
of the NCO requires that CIN be set at a logic 0. When
CIN is set at a logic 1 the effective value of the ∆-Phase
register is increased by one. This allows the resolution
of the accumulator to be expanded for higher
frequency resolution.
R O U N D
COS11-0=2047 x cos (360 x (phase+0.5)/8192)°+2048
The ROUND input controls the precision of the
SINE11-0 and COS11-0 outputs. When the ROUND
input is set high, the sine and cosine signals appearing
on the SINE11-0 and COS11-0 buses are accurate to 12
bits. In some instances it may be desirable to use only
the 8 MSBs of these outputs. In such circumstances
the outputs appearing on the SINE11-0 and COS11-0
buses can be rounded to present a more accurate 8-bit
representation of the signal by setting the ROUND
input low.
The result is accurate to within 1 LSB. However, when
ROUND is set low, the value appearing on the COS11-
outputs will be rounded and will follow the
0
relationship:
COS11-4=127 x cos (360 x (phase+0.5)/8192)°+128
The data appearing on the COS3-0 outputs will not be
meaningful under these circumstances.
S Y N C
C O S E N
The Sync output indicates the instant in time when
The Cosine Enable input controls the power supply to
the frequency, FM, or PM change made at the inputs
affects the SINE11-0 and COS11-0 output signals. The
normally high SYNC output goes low for one clock
cycle 19 clock cycles after an FRLD or FMLD
command, and 12 clock cycles after a PHLD
command, to indicate the end of the pipeline delay
and the start of the new steady state condition.
the Cosine Lookup Table. When it is low the cosine
lookup table in the STEL-1177 is disabled, and only
the SINE11-0 outputs will be valid. This reduces the
power consumption of the device by approximately
30%.
OUTPUT
SIGNALS
F M S Y N C
The FM Sync output indicates the instant in time when
SINE11-0
the FM data on the FMOD bus is written into the
device. The FMSYNC output is normally high and
goes low for one clock cycle at a frequency depending
on the state of the RATE1-0 inputs. In the automatic
modulation modes (RATE1-0 ≠ 00) the data on the
FMOD15-0 bus will be written into the FM Buffer
Register on the rising edge of the clock following the
falling edge of FMSYNC. This signal can be used to
synchronize the updating of the FM data externally.
The signal appearing on the SINE11-0 outputs is
derived from the 13 most significant bits of the Phase
Accumulator. The 12-bit sine function is presented in
offset binary format. When the phase accumulator is
zero, e.g., after a reset, the decimal value of the output
is 2049 (801H). When the phase modulation is zero the
value of the output for a given phase value follows the
relationship:
SINE11-0=2047 x sin (360 x (phase+0.5)/8192)°+2048
The result is accurate to within 1 LSB. However, when
ROUND is set low, the value appearing on the
SINE11-0 outputs will be rounded and will follow the
relationship:
SINE11-4=127 x sin (360 x (phase+0.5)/8192)°+128
The data appearing on the SINE3-0 outputs will not be
meaningful under these circumstances.
STEL-1177
8
Powered by ICminer.com Electronic-Library Service CopyRight 2003
ELECTRICAL
CHARACTERISTICS
ABSOLUTE
MAXIMUM
RATINGS
Warning: Stresses greater than those shown below may cause permanent damage to the device.
Exposure of the device to these conditions for extended periods may also affect device reliability.
All voltages are referenced to VSS.
Symbol
Parameter
Range
Units
Tstg
Storage Temperature
–40 to +125
–65 to +150
–0.3 to + 7
–0.3 to VDD + 0.3
± 10
°C (Plastic package)
°C (Ceramic package)
VDDmax
VI(max)
Ii
Supply voltage on VDD
Input voltage
volts
volts
mA
DC input current
RECOMMENDED
OPERATING
CONDITIONS
Symbol
Parameter
Range Units
VDD
Supply Voltage
+5 ± 5%
Volts (Commercial)
Volts (Military)
+5 ± 10%
0 to +70
–55 to +125
Ta
Operating Temperature (Ambient)
°C
°C
(Commercial)
(Military)
D.C. CHARACTERISTICS (Operating Conditions: VDD= 5.0 V ±5%, VSS = 0 V, Ta= 0° to 70° C, Commercial
DD= 5.0 V ±10%, VSS = 0 V, Ta = –55° to 125° C, Military)
V
Symbol
Parameter
Min. Typ.
Max. Units
Conditions
IDD(Q)
IDD
Supply Current, Quiescent
Supply Current, Operational
High Level Input Voltage
Standard Operating Conditions
Extended Operating Conditions
Low Level Input Voltage
High Level Input Current
High Level Input Current
Low Level Input Current
Low Level Input Current
High Level Output Voltage
Low Level Output Voltage
Output Short Circuit Current
1.0 mA
Static, no clock
7.0
mA/MHz
VIH(min)
2.0
volts
volts
Logic '1'
2.25
Logic '1'
VIL(max)
IIH(min)
IIH(min)
IIL(max)
IIL(max)
VOH(min)
VOL(max)
IOS
0.8 volts
110 µA
10 µA
Logic '0'
10
35
CIN and CSEL, VIN = VDD
All other inputs, VIN = VDD
CIN and CSEL, VIN = VSS
All other inputs, VIN = VSS
IO = –4.0 mA
–10 µA
–130 µA
volts
–15
2.4
–45
4.5
0.2
65
0.4 volts
130 mA
–130 mA
IO = +4.0 mA
20
VOUT = VDD, VDD = max
VOUT = VSS, VDD = max
–10
–45
CIN
COUT
Input Capacitance
Output Capacitance
2
4
pF
pF
All inputs
All outputs
9
STEL-1177
Powered by ICminer.com Electronic-Library Service CopyRight 2003
NCO RESET SEQUENCE
tRS
RESET
CLOCK
6 CLOCK
EDGES
1
2
3
4
5
6
SINE 11-0
COS 11-0
NOT VALID
801H
NCO FREQUENCY CHANGE SEQUENCE
CSEL
ADDR 3-0
WRSTB
DATA 7-0
CLOCK
DON'T CARE
DON'T CARE
tSU
tHD
tWR
DON'T CARE
DON'T CARE
19 CLOCK
EDGES
tSU
tCH
tCL
FRLD
tW
FSYNC
tCD
OLD FREQUENCY NEW FREQUENCY
SINE 11-0
COS 11-0
STEL-1177
10
Powered by ICminer.com Electronic-Library Service CopyRight 2003
NCO PHASE CHANGE SEQUENCE
1. PHSEL=0. DIRECT LOADING.
12 CLOCK EDGES
CLOCK
tSU
DATA 7-0
DON'T CARE
DON'T CARE
ADDR 3-0
tHD
tSU
PHLD
tW
PSYNC
OLD PHASE
NEW PHASE
SINE 11-0
COS 11-0
ELECTRICAL
CHARACTERISTICS
A.C. CHARACTERISTICS (Operating Conditions: VDD= 5.0 V ± 5%, VSS=0 V, Ta= 0° to 70° C, Commercial
VDD= 5.0 V ± 10%, VSS=0 V, Ta=–55° to 125° C, Military)
Commercial
Military
Symbol
Parameter
Min. Typ. Max. Min. Typ. Max. Units Conditions
tRS
tSR
tSU
RESET pulse width
20
10
5
25
12
5
nsec.
nsec.
nsec.
RESET to CLOCK Setup
DATA, ADDR or CSEL
to WRSTB or PHLD Setup
and FRLD, PHLD, FMLD
or FMOD to CLOCK Setup
DATA, ADDR or CSEL
to WRSTB or PHLD Hold
and FRLD, PHLD, FMLD
or FMOD to CLOCK Hold
tHD
5
5
nsec.
11
STEL-1177
Powered by ICminer.com Electronic-Library Service CopyRight 2003
NCO PHASE CHANGE SEQUENCE
2. PHSEL=1. BUS LOADING.
CSEL
ADDR 3-0
WRSTB
DATA 7-0
DON'T CARE
DON'T CARE
tSU
tHD
tWR
DON'T CARE
DON'T CARE
12 CLOCK
EDGES
CLOCK
PHLD
tSU
tW
PSYNC
OLD PHASE
NEW PHASE
SINE 11-0
COS 11-0
ELECTRICAL
CHARACTERISTICS
A.C. CHARACTERISTICS (Operating Conditions: VDD= 5.0 V ± 5%, VSS=0 V, Ta= 0° to 70° C, Chimerical
VDD= 5.0 V ± 10%, VSS=0 V, Ta=–55° to 125° C, Military)
Commercial
Military
Symbol
Parameter
Min. Typ. Max. Min. Typ. Max. Units Conditions
tCH
CLOCK high
5
5
5
7
nsec.
nsec.
nsec.
nsec.
nsec.
fCLK = 60 MHz
fCLK = 40 MHz
fCLK = 60 MHz
fCLK = 40 MHz
8
tCH
tW
CLOCK low
8
8
WRSTB, FRLD, PHLD
or FMLD pulse width
CLOCK to output delay
(All outputs)
tCD
12
12
3
20
nsec.
Load = 15 pF
STEL-1177
Powered by ICminer.com Electronic-Library Service CopyRight 2003
NCO FREQUENCY MODULATION SEQUENCE
1. RATE = 00. MANUAL LOADING.
19 CLOCK EDGES
CLOCK
tHD
tSU
FMOD 15-0
FMLD
DON'T CARE
VALID
DON'T CARE
tSU
tW
FMSYNC
SYNC
tCD
NEW FREQUENCY
OLD FREQUENCY
SINE 11-0
COS 11-0
2. RATE ≠ 00. AUTOMATIC LOADING.
(RATE = 01 shown)
4 CLOCK CYCLES
CLOCK
FMOD 15-0
DON'T CARE
VALID
tHD
DON'T CARE
VALID
DON'T CARE
tSU
FMSYNC
SINE 11-0
COS 11-0
FMLD
13
STEL-1177
Powered by ICminer.com Electronic-Library Service CopyRight 2003
HIGH-SPEED
FREQUENCY
CHANGE
The frequency of the STEL-1177 NCO can be changed
as rapidly as 25% of the clock frequency. This is done
by synchronizing the writing to the two ∆-Phase
Buffer Registers, and updating both every eight clock
cycles. The timing for this procedure is shown below.
Each ∆-Phase Buffer Register is loaded while the
contents of the other are being transferred into the
ALU Buffer Register. The sequence for a load cycle
begins on the rising edge of the clock following a
falling edge of FRLD (or a falling edge of FMLD if
SIMLD is high). In the diagram below, ∆-Phase Buffer
Register A is being loaded in clock cycles 1 through 4,
while the contents of ∆-Phase Buffer Register B are
being transferred, because FRSEL was low during the
falling edge of FRLD. The reverse process happens
during clock cycles 5 through 8, and the process then
repeats starting in clock cycle 9. The FRLD signal can
be used to clock a bistable latch to generate the FRSEL
signal. The maximum update rate is 25%.
1
2
3
4
5
6
7
8
9
CLOCK
WRSTB
ADDR
0111
0000
0001
0010
0011
0100
0101
0110
0111
0000
FRLD
FRSEL
be slightly more than half the clock period at high
speeds some advantage can be gained by generating
the clock by inverting the WRSTB signal, rather than
the other way around. This makes the propagation
delay of the inverter used work for the timing
requirements instead of against them, since the hold
time requirement from the previous rising edge of the
clock (tHD) is 2 nsec.
It is possible to update the frequency at up to 25% of
the clock frequency using only one buffer register. The
timing for this procedure is shown in the diagram
below, and must be adhered to rigorously in order to
assure adequate setup and hold times. The most
critical factor is the setup time (tSU) for the WRSTB
relative to the clock (rising edge to rising edge). This
must be 8 nsec. for correct operation. Since this may
1
2
3
4
5
6
7
8
9
CLOCK
tSU
tHD
WRSTB
ADDR
0001 0010
0011
0000
0001
0010
0011
0000
0001
3-0
FRLD
FRSEL=1
STEL-1177
14
Powered by ICminer.com Electronic-Library Service CopyRight 2003
APPLICATIONS
INFORMATION
USING THE STEL-1177
IN A HIGH-SPEED
WRITE
WRSTB
FRLD
FREQ. LOAD
PHASE
MODULATOR
FROM
µC
By routing the data and address
lines from the microcontroller via
2:1 multiplexers (e.g. 74HC157)
the MNCO can be set up from the
microcontroller and then phase
modulated at high-speed from an
external source. The PHSEL line
should be set to a logic 0 to enable
this mode of operation. The
4
4
DATA
0-7
A
D0
.
.
ADDR
0-3
B
A/B
D3
4
4
A
D4
.
STEL-1177
MNCO
.
PHASE
0-11
B
A/B
D7
4
4
FROM
PHASE
MOD.
A
A0
.
.
system shown modulates all 12
bits. In a typical PSK system only
1 to 4 bits of modulation will be
used, simplifying the system
considerably.
B
A/B
FREQ./PH SEL
PHASE LOAD
A3
PHLD
APPLICATION EXAMPLE
-
A
HIGH-LINEARITY FM CARRIER GENERATOR
CONTROL
PROC-
ESSOR
STEL-
1177
NCO
SINE
12
BPF
12-25
MHz
95-108 MHz
BPF
95-108
MHz
D/A
FREQUENCY
MODULATOR
CLK
120 MHz
OSCILLATOR
÷2
The STEL-1177 can be used for high-linearity frequency modulation. The FM port has 16-bit resolution and
linearity, and this can be used to generate a very high-quality signal for FM broadcasting in the 88-108 MHz
frequency band. The audio signal can be digitized at a very high sampling rate, either directly or by
interpolation, to maximize the performance capability of the system.
SPECTRAL
PURITY
The sine and cosine signals generated by the STEL-
1177 have 12 bits of amplitude resolution and 13 bits
of phase resolution which results in spurious levels
which are theoretically at least 75 dB down. The
highest output frequency the NCO can generate is half
the clock frequency (fc/2), and the spurious
components at frequencies greater than fc/2 can be
removed by filtering. As the output frequency fo of
In many applications the NCO is used with a digital
to analog converter (DAC) to generate an analog
waveform which approximates an ideal sinewave.
The spectral purity of this synthesized waveform is a
function of many variables including the phase and
amplitude quantization, the ratio of the clock
frequency to output frequency, and the dynamic
characteristics of the DAC.
15
STEL-1177
Powered by ICminer.com Electronic-Library Service CopyRight 2003
the NCO approaches fc/2, the "image" spur at fc– fo
(created by the sampling process) also approaches
fc/2 from above. If the programmed output frequency
is very close to fc/2 it will be virtually impossible to
remove this image spur by filtering. For this reason,
the maximum practical output frequency of the NCO
should be limited to about 40% of the clock frequency.
the second harmonic frequency will be higher than the
Nyquist frequency, 50% of the clock frequency. When
this happens, the image of the harmonic at the
frequency fc– 2fo, which is not harmonically related to
the output signal, will become intrusive since its
frequency falls as the output frequency rises,
eventually crossing the fundamental output when its
frequency crosses through fc/3. It would be necessary
to select a DAC with better dynamic linearity to
improve the harmonic spur levels. (The dynamic
linearity of a DAC is a function of both its static
linearity and its dynamic characteristics, such as
settling time and slew rates.) At higher output
frequencies the waveform produced by the DAC will
have large output changes from sample to sample. For
this reason, the settling time of the DAC should be
short in comparison to the clock period. As a general
rule, the DAC used should have the lowest possible
glitch energy as well as the shortest possible settling
time.
A spectral plot of the NCO output after conversion
with a DAC (Sony CX20202A-1) is shown below. In
this case, the clock frequency is 60 MHz and the output
frequency is programmed to 6.789 MHz. This 10-bit
DAC gives better performance than any of the
currently available 12-bit DACs at clock frequencies
higher than 10 or 20 MHz. The maximum non-
harmonic spur level observed over the entire useful
output frequency range in this case is –74 dBc. The
spur levels are limited by the dynamic linearity of the
DAC. It is important to remember that when the
output frequency exceeds 25% of the clock frequency,
TYPICAL
Center Frequency:
SPECTRUM
6.7 MHz
Frequency Span:
Reference Level:
10.0 MHz
–5 dBm
Resolution Bandwidth: 1 KHz
Video Bandwidth:
Scale:
3 kHz
Log, 10 dB/div
6.789 MHz
60 MHz
Output frequency:
Clock frequency:
STEL-1177
16
Powered by ICminer.com Electronic-Library Service CopyRight 2003
Information in this document is provided in connection with
Intel® products. No license, express or implied, by estoppel
or otherwise, to any intellectual property rights is granted by
this document. Except as provided in Intels Terms and Con-
ditions of Sale for such products, Intel assumes no liability
whatsoever, and Intel disclaims any express or implied
warranty, relating to sale and/or use of Intel® products in-
cluding liability or warranties relating to fitness for a particu-
lar purpose, merchantability, or infringement of any patent,
copyright or other intellectual property right. Intel products
are not intended for use in medical, life saving, or life sus-
taining applications.
Intel may make changes to specifications and product de-
scriptions at any time, without notice.
For Further Information Call or Write
INTEL CORPORATION
Cable Network Operation
350 E. Plumeria Drive, San Jose, CA 95134
Customer Service Telephone: (408) 545-9700
Technical Support Telephone: (408) 545-9799
FAX: (408) 545-9888
Copyright © Intel Corporation, December 15, 1999. All rights reserved
Powered by ICminer.com Electronic-Library Service CopyRight 2003
相关型号:
©2020 ICPDF网 联系我们和版权申明