TS61ID [ETC]
Voltage-Feedback Operational Amplifier ; 电压反馈运算放大器\n
| 型号： | TS61ID |
| 厂家： | 
ETC |
| 描述： | Voltage-Feedback Operational Amplifier
|
| 文件： | 总9页 (文件大小：103K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
TS613
DUAL WIDE BAND OPERATIONAL AMPLIFIER
WITH HIGH OUTPUT CURRENT
■ LOW NOISE : 3nV/√Hz, 1.2pA/√Hz
■ HIGH OUTPUT CURRENT : 200mA
■ VERY LOW HARMONIC AND INTERMODU-
LATION DISTORTION
■ HIGH SLEW RATE : 40V/µs
■ SPECIFIED FOR 25Ω LOAD
D
SO-8
DESCRIPTION
(Plastic Micropackage)
The TS613 is a dual operational amplifier featur-
ing a high output current (200mA min.), large
gain-bandwidth product (130MHz) and capable of
driving a 25Ω load with a 160mA output current at
±6V power supply.
PIN CONNECTIONS (top view)
This device is particularly intended for applications
where multiple carriers must be amplified simulta-
neously with very low intermodulation products.
The TS613 is housed in a SO8 package.
APPLICATION
■ UPSTREAM line driver for Assymetric Digital
Subscriber Line (ADSL) (NT).
ORDER CODE
Package
Part Number
Temperature Range
D
TS613ID
-40, +85°C
•
D = Small Outline Package (SO) - also available in Tape & Reel (DT)
May 2000
1/9
TS613
ABSOLUTE MAXIMUM RATINGS
Symbol
Parameter
Value
Unit
1)
V
±7
±2
V
V
Supply voltage
CC
2)
V
Differential Input Voltage
id
in
3)
V
±6
V
Input Voltage Range
T
Operating Free Air Temperature Range TS612ID
Storage Temperature
-40 to + 85
-65 to +150
150
°C
oper
T
°C
std
T
Maximum Junction Temperature
°C
j
R
Thermal Resistance Junction to Case
Thermal Resistance Junction to Ambient Area
Maximum Power Dissipation (@25°C)
Output Short Circuit Duration
28
°C/W
°C/W
mW
thjc
R
175
tha
Pmax.
715
4)
1. All voltages values, except differential voltage are with respect to network terminal.
2. Differential voltages are non-inverting input terminal with respect to the inverting input terminal.
3. The magnitude of input and output voltages must never exceed V
CC
+0.3V.
4. An output current limitation protects the circuit from transient currents. Short-circuits can cause excessive heating.
Destructive dissipation can result from short circuit on amplifiers.
OPERATING CONDITIONS
Symbol
Parameter
Value
±2.5 to ±6
Unit
V
V
Supply Voltage
Common Mode Input Voltage
CC
+
V
V
(V ) +2 to (V
) -1
CC
icm
CC
2/9
TS613
ELECTRICAL CHARACTERISTICS. VCC = ±6V, Tamb = 25°C (unless otherwise specified).
Symbol
Parameter
Test Condition
Min.
Typ.
Max
Unit
DC PERFORMANCE
Tamb
-6
-1
6
10
6
Vio
∆Vio
Iio
Input Offset Voltage
mV
mV
µA
Tmin. < Tamb < Tmax.
Tamb = 25°C
Tamb
Differential Input Offset Voltage
Input Offset Current
0.2
5
3
T
min. < Tamb < Tmax.
5
Tamb
15
30
Iib
Input Bias Current
µA
T
min. < Tamb < Tmax.
V
ic = 2V to 2V, Tamb
min. < Tamb < Tmax.
ic = ±6V to ±4V, Tamb
min. < Tamb < Tmax.
No load, Vout = 0
90
70
70
50
108
88
11
CMR
Common Mode Rejection Ratio
dB
T
V
SVR
ICC
Supply Voltage Rejection Ratio
Total Supply Current per Operator
dB
T
15
-4
mA
DYNAMIC PERFORMANCE
VOH
I
I
out = 160mA, RL to GND
out = 160mA, RL to GND
High Level Output Voltage
4
4.5
V
V
VOL
Low Level Output Voltage
-4.5
Vout = 7V peak
RL = 25Ω, Tamb
6500
5000
11000
130
AVD
Large Signal Voltage Gain
Gain Bandwidth Product
V/V
T
min. < Tamb < Tmax.
A
VCL = +11, f = 20MHz
GBP
80
23
MHz
RL = 100Ω
AVCL = +7, RL = 50Ω
SR
Iout
Slew Rate
40
V/µs
Output Short Circuit Current
±320
mA
Vic = ±6V, Tamb
+200
+180
Isink
Output Sink Current
mA
mA
Tmin. < Tamb < Tmax.
Vic = ±6V, Tamb
-200
-180
Isource
Output Source Current
Tmin. < Tamb < Tmax.
RL = 25Ω//15pF
RL = 25Ω//15pF
Phase Margin at AVCL = 14dB
Phase Margin at AVCL = 6dB
ΦM14
ΦM6
60
40
°
°
NOISE AND DISTORTION
en
Equivalent Input Noise Voltage
f = 100kHz
3
nV/√Hz
pA/√Hz
in
Equivalent Input Noise Current
Total Harmonic Distorsion
f = 100kHz
Vout = 4Vpp, f = 100kHz
AVCL = -10
1.2
THD
HD2-10
HD2+2
HD3+2
IM2-10
IM3-10
-69
dB
RL = 25Ω//15pF
Vout = 4Vpp, f = 100kHz
AVCL = -10
Load =25Ω//15pF
Vout = 4Vpp, f = 100kHz
AVCL = +2
Load =25Ω//15pF
Vout = 4Vpp, f = 100kHz
AVCL = +2
2nd Harmonic Distorsion
-70
-74
-79
-77
-77
dBc
dBc
dBc
dBc
dBc
2nd Harmonic Distorsion
3rd Harmonic Distorsion
Load =25Ω//15pF
F1 = 80kHz, F2 = 70kHz
Vout = 8Vpp, AVCL = -10
Load = 25Ω//15pF
2nd Order Intermodulation Product
3rd Order Intermodulation Product
F1 = 80kHz, F2 = 70kHz
Vout = 8Vpp, AVCL = -10
Load = 25Ω//15pF
3/9
TS613
INTERMODULATION DISTORTION
The curves shown below are the measurements results of a single operator wired as an adder with a gain
of 15dB.
The operational amplifier is supplied by a symmetric ±6V and is loaded with 25Ω.
Two synthesizers (Rhode & Schwartz SME) generate two frequencies (tones) (70 & 80kHz ; 180 &
280kHz).
An HP3585 spectrum analyzer measures the spurious level at different frequencies.
The curves are traced for different output levels (the value in the X ax is the value of each tone).
The output levels of the two tones are the same.
The generators and spectrum analyzer are phase locked to enhance measurement precision.
3rd ORDER INTERMODULATION
Gain=15dB, Vcc=±6V, RL=25Ω, 2 tones 70kHz/
80kHz
3rd ORDER INTERMODULATION
Gain=15dB, Vcc=±6V, RL=25Ω, 2 tones 180kHz/
280kHz
0
-10
-20
-30
-40
0
-10
-20
-30
-40
90kHz
-50
-50
80kHz
-60
230kHz
-60
380kHz
-70
-70
-80
-80
640kHz
60kHz
-90
-90
740kHz
220kHz
-100
-100
1
1,5
2
2,5
3
3,5
4
4,5
1
1,5
2
2,5
3
3,5
4
4,5
Vout peak (V)
Vout peak (V)
2nd ORDER INTERMODULATION
Gain=15dB, Vcc=±6V, RL=25Ω, 2 tones 180kHz/
280kHz, Spurious measurement @100kHz
-55
-60
-65
-70
1,5
2
2,5
3
3,5
4
4,5
Vout peak (V)
4/9
TS613
Closed Loop Gain and Phase vs. Frequency
Closed Loop Gain and Phase vs. Frequency
Gain=+2, Vcc=±6V, RL=25Ω
Gain=+6, Vcc=±6V, RL=25Ω
10
0
200
20
200
100
0
Gain
Gain
15
100
0
10
5
Phase
0
Phase
-10
-20
-30
-5
-10
-15
-20
-100
-200
-100
-200
10kHz
100kHz
1MHz
10MHz
100MHz
10kHz
100kHz
1MHz
10MHz
100MHz
Frequency
Frequency
Closed Loop Gain and Phase vs. Frequency
Equivalent Input Voltage Noise
Gain=+11, Vcc=±6V, RL=25Ω
Gain=+100, Vcc=±6V, no load
30
20
10
0
200
20
15
10
5
Gain
+
_
100
0
10k
Phase
100
-10
-20
-30
-100
-200
0
100Hz
1kHz
10kHz
100kHz
1MHz
10kHz
100kHz
1MHz
10MHz
100MHz
Frequency
Frequency
Maximum Output Swing
Channel Separation (Xtalk) vs. Frequency
Vcc=±6V, RL=25Ω
XTalk=20Log(V2/V1), Vcc=±6V, RL=25Ω
-20
5
4
3
2
VIN
+
49.9Ω
output
_
V1
-30
-40
-50
-60
-70
-80
1kΩ
1kΩ
100Ω
100Ω
25Ω
input
1
+
49.9Ω
0
_
V2
-1
-2
-3
-4
-5
25Ω
0
2
4
6
Time (µs)
8
10
100kHz
1MHz
10MHz
10kHz
Frequency
5/9
TYPICAL APPLICATION : TS613 AS DRIVER
FOR ADSL LINE INTERFACES
A SINGLE SUPPLY IMPLEMENTATION WITH PASSIVE
OR ACTIVE IMPEDANCE MATCHING
by C. PRUGNE
ADSL CONCEPT
The TS613 is used as a dual line driver for the up-
stream signal.
Asymmetric Digital Subscriber Line (ADSL), is a
new modem technology, which converts the exist-
ing twisted-pair telephone lines into access paths
for multimedia and high speed data communica-
tions.
For the remote terminal it is required to create an
ADSL modem easy to plug in a PC. In such an ap-
plication, the driver should be implemented with a
+12 volts single power supply. This +12V supply is
available on PCI connector of purchase.
The figure 2 shows a single +12V supply circuit
that uses the TS613 as a remote terminal trans-
mitter in differential mode.
ADSL transmits more than 8 Mbps to a subscriber,
and can reach 1Mbps from the subscriber to the
central office. ADSL can literally transform the ac-
tual public information network by bringing mov-
ies, television, video catalogs, remote CD-ROMs,
LANs, and the Internet into homes.
Figure 2 : TS613 as a differential line driver with
a +12V single supply
An ADSL modem is connected to a twisted-pair
telephone line, creating three information chan-
nels: a high speed downstream channel (up to
1.1MHz) depending on the implementation of the
ADSL architecture, a medium speed upstream
channel (up to 130kHz) and a POTS (Plain Old
Telephone Service), split off from the modem by
filters.
1µ
100n
8
3
+12V
1
+
10n
12.5
_
2
+12V
1k
1:2
Vi
Vi
R2
47k
Vo
Vo
Hybrid
&
R1
25Ω
100Ω
Transformer
10µ
100n
47k
R3
1k
_
+
6
5
GND
12.5
7
GND
THE LINE INTERFACE - ADSL Remote
Terminal (RT):
4
100n
The Figure1 shows a typical analog line interface
used for ADSL. The upstream and downstream
signals are separated from the telephone line by
using an hybrid circuit and a line transformer. On
this note, the accent will be made on the emission
path.
The driver is biased with a mid supply (nominaly
+6V), in order to maintain the DC component of
the signal at +6V. This allows the maximum dy-
namic range between 0 and +12 V. Several op-
tions are possible to provide this bias supply (such
as a virtual ground using an operational amplifier),
such as a two-resistance divider which is the
cheapest solution. A high resistance value is re-
quired to limit the current consumption. On the
other hand, the current must be high enough to
bias the inverting input of the TS613. If we consid-
er this bias current (5µA) as the 1% of the current
through the resistance divider (500µA) to keep a
stable mid supply, two 47kΩ resistances can be
used.
Figure 1 : Typical ADSL Line Interface
high output
current
upstream
LPfilter
digital to
analog
emission
(analog)
impedance
matching
TS613
Line Driver
digital
treatment
HYBRID
CIRCUIT
twisted-pair
telephone
line
The input provides two high pass filters with a
break frequency of about 1.6kHz which is neces-
sary to remove the DC component of the input sig-
nal. To avoid DC current flowing in the primary of
the transformer, an output capacitor is used. The
analogto
digital
reception
circuits
downstream
reception
(analog)
6/9
TS613
1µF capacitance provides a path for low frequen-
cies, the 10nF capacitance provides a path for
high end of the spectrum.
Component calculation:
Let us consider the equivalent circuit for a single
ended configuration, figure4.
In differential mode the TS613 is able to deliver a
typical amplitude signal of 18V peak to peak.
Figure 4 : Single ended equivalent circuit
The dynamic line impedance is 100Ω. The typical
value of the amplitude signal required on the line
is up to 12.4V peak to peak. By using a 1:2 trans-
former ratio the reflected impedance back to the
primary will be a quarter (25Ω) and therefore the
amplitude of the signal required with this imped-
ance will be the half (6.2 V peak to peak). Assum-
ing the 25Ω series resistance (12.5Ω for both out-
puts) necessary for impedance matching, the out-
put signal amplitude required is 12.4 V peak to
peak. This value is acceptable for the TS613. In
this case the load impedance is 25Ω for each driv-
er.
+
Rs1
Vi
_
Vo°
Vo
R2
-1
R3
1/2
R1
1/2
RL
Let us consider the unloaded system. Assuming
the currents through R1, R2 and R3
as respectively:
For the ADSL upstream path, a lowpass filter is
absolutely necessary to cutoff the higher frequen-
cies from the DAC analog output. In this simple
non-inverting amplification configuration, it will be
easy to implement a Sallen-Key lowpass filter by
using the TS613. For ADSL over POTS, a maxi-
mum frequency of 135kHz is reached. For ADSL
over ISDN, the maximum frequency will be
276kHz.
2Vi (Vi – Vo°)
(Vi + Vo)
-------- --------------------------
-----------------------
and
,
R1
R2
R3
As Vo° equals Vo without load, the gain in this
case becomes :
2 R 2 R 2
1 + ---------- + ------
Vo(noload)
R 1 R 3
R2
R3
G = ------------------------------ = ----------------------------------
Vi
1 – ------
The gain, for the loaded system will be (1):
INCREASING THE LINE LEVEL BY USING AN
ACTIVE IMPEDANCE MATCHING
2 R 2 R 2
1 + ---------- + ------
1
2
R 1 R 3
Vo(withload)
-- ----------------------------------
GL = ----------------------------------- =
,(1 )
With passive matching, the output signal ampli-
tude of the driver must be twice the amplitude on
the load. To go beyond this limitation an active
maching impedance can be used. With this tech-
nique it is possible to keep good impedance
matching with an amplitude on the load higher
than the half of the ouput driver amplitude. This
concept is shown in figure3 for a differential line.
R2
Vi
1 – ------
R3
As shown in figure5, this system is an ideal gener-
ator with a synthesized impedance as the internal
impedance of the system. From this, the output
voltage becomes:
Vo = (ViG) – (RoIout),(2)
Figure 3 : TS613 as a differential line driver with
with Ro the synthesized impedance and Iout the
output current. On the other hand Vo can be ex-
pressed as:
an active impedance matching
2R2 R 2
1µ
Vi 1 + ---------- + ------
100n
R1 R 3
8
Rs1Iout
3
2
+12V
1
+
_
10n
12.5
---------------------
Vo = ---------------------------------------------- –
,(3 )
R2
R2
+12V
1 – ------
1 – ------
1k
R3
R3
Vo°
1:2
Vi
Vi
R2
47k
Vo
Hybrid
&
Transformer
R3
R5
25Ω
100Ω
R1
10µ
100n
47k
Vo
R4
Vo°
12.5
1k
_
+
6
5
GND
7
GND
4
100n
7/9
TS613
By identification of both equations (2) and (3), the
synthesized impedance is, with Rs1=Rs2=Rs:
GL (gain for the
loaded system)
GL is fixed for the application requirements
Rs
GL=Vo/Vi=0.5(1+2R2/R1+R2/R3)/(1-R2/R3)
2R2/[2(1-R2/R3)GL-1-R2/R3]
Abritrary fixed
----------------
Ro =
,(4 )
R2
R1
1 – ------
R3
R2 (=R4)
R3 (=R5)
Rs
R2/(1-Rs/0.5RL)
Figure 5 : Equivalent schematic. Ro is the syn-
0.5RL(k-1)
thesized impedance
CAPABILITIES
The table below shows the calculated compo-
nents for different values of k. In this case
R2=1000Ω and the gain=16dB. The last column
displays the maximum amplitude level on the line
regarding the TS613 maximum output capabilities
(18Vpp diff.) and a 1:2 line transformer ratio.
Iout
Ro
Vi.Gi
1/2RL
Active matching
TS613 Output
Level to get
12.4Vpp on
the line
Maximum
Line level
(Vpp diff)
R1
(Ω)
R3
(Ω)
Rs
(Ω)
Unlike the level Vo° required for a passive imped-
ance, Vo° will be smaller than 2Vo in our case. Let
us write Vo°=kVo with k the matching factor vary-
ing between 1 and 2. Assuming that the current
through R3 is negligeable, it comes the following
resistance divider:
k
(Vpp diff)
1.3
1.4
1.5
1.6
1.7
820 1500 3.9
490 1600 5.1
360 2200 6.2
270 2400 7.5
240 3300 9.1
Passive matching
8
27.5
25.7
25.3
23.7
22.3
18
8.7
9.3
kVoRL
Ro = ---------------------------
9.9
RL + 2Rs1
After choosing the k factor, Rs will equal to
1/2RL(k-1).
10.5
12.4
MEASUREMENT OF THE POWER
CONSUMPTION IN THE ADSL APPLICATION
A good impedance matching assumes:
1
--
Ro = RL,(5)
Conditions:
2
Passive impedance matching
Transformer turns ratio: 2
From (4) and (5) it becomes:
2 Rs
RL
R2
R3
Maximun level required on the line: 12.4Vpp
Maximum output level of the driver: 12.4Vpp
Crest factor: 5.3 (Vp/Vrms)
The TS613 power consumption during emission
on 900 and 4550 meter twisted pair telephone
lines: 360mW
---------
------ = 1 –
,(6 )
By fixing an arbitrary value for R2, (6) gives:
R2
R3 = -------------------
2Rs
1 – ---------
RL
Finally, the values of R2 and R3 allow us to extract
R1 from (1), and it comes:
2 R 2
---------------------------------------------------------
R 1 =
,(7 )
R2
R2
2 1 – ------ GL – 1 – ------
R3 R3
with GL the required gain.
8/9
TS613
PACKAGE MECHANICAL DATA
8 PINS - PLASTIC MICROPACKAGE (SO)
Millimeters
Dim.
Inches
Typ.
Min.
Typ.
Max.
Min.
Max.
A
a1
a2
a3
b
1.75
0.25
1.65
0.85
0.48
0.25
0.5
0.069
0.010
0.065
0.033
0.019
0.010
0.020
0.1
0.004
0.65
0.35
0.19
0.25
0.026
0.014
0.007
0.010
b1
C
c1
D
45° (typ.)
4.8
5.8
5.0
6.2
0.189
0.228
0.197
0.244
E
e
1.27
3.81
0.050
0.150
e3
F
3.8
0.4
4.0
1.27
0.6
0.150
0.016
0.157
0.050
0.024
L
M
S
8° (max.)
Information furnished is believed to be accurate and reliable. However, STMicroelectronics assumes no responsibility for the
consequences of use of such information nor for any infringement of patents or other rights of third parties which may result from
its use. No license is granted by implication or otherwise under any patent or patent rights of STMicroelectronics. Specifications
mentioned in this publication are subject to change without notice. This publication supersedes and replaces all information
previously supplied. STMicroelectronics products are not authorized for use as critical components in life support devices or
systems without express written approval of STMicroelectronics.
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