HA1-2556-9 [INTERSIL]
57MHz, Wideband, Four Quadrant, Voltage Output Analog Multiplier; 57MHz ，宽带，四象限电压输出模拟乘法器
| 型号： | HA1-2556-9 |
| 厂家： | 
Intersil |
| 描述： | 57MHz, Wideband, Four Quadrant, Voltage Output Analog Multiplier |
| 文件： | 总15页 (文件大小：246K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
HA-2556
Data Sheet
September 1998
File Number 2477.5
57MHz, Wideband, Four Quadrant,
Voltage Output Analog Multiplier
Features
• High Speed Voltage Output . . . . . . . . . . . . . . . . . 450V/µs
• Low Multiplication Error . . . . . . . . . . . . . . . . . . . . . . .1.5%
• Input Bias Currents. . . . . . . . . . . . . . . . . . . . . . . . . . . 8µA
• 5MHz Feedthrough. . . . . . . . . . . . . . . . . . . . . . . . . .-50dB
• Wide Y Channel Bandwidth . . . . . . . . . . . . . . . . . . 57MHz
• Wide X Channel Bandwidth . . . . . . . . . . . . . . . . . . 52MHz
The HA-2556 is a monolithic, high speed, four quadrant,
analog multiplier constructed in the Intersil Dielectrically
Isolated High Frequency Process. The voltage output
simplifies many designs by eliminating the current-to-voltage
conversion stage required for current output multipliers. The
HA-2556 provides a 450V/µs slew rate and maintains
52MHz and 57MHz bandwidths for the X and Y channels
respectively, making it an ideal part for use in video systems.
• V 0.1dB Gain Flatness . . . . . . . . . . . . . . . . . . . . 5.0MHz
Y
The suitability for precision video applications is
Applications
demonstrated further by the Y Channel 0.1dB gain flatness
to 5.0MHz, 1.5% multiplication error, -50dB feedthrough and
differential inputs with 8µA bias current. The HA-2556 also
• Military Avionics
• Missile Guidance Systems
• Medical Imaging Displays
• Video Mixers
o
has low differential gain (0.1%) and phase (0.1 ) errors.
The HA-2556 is well suited for AGC circuits as well as mixer
applications for sonar, radar, and medical imaging
equipment. The HA-2556 is not limited to multiplication
applications only; frequency doubling, power detection, as
well as many other configurations are possible.
• Sonar AGC Processors
• Radar Signal Conditioning
• Voltage Controlled Amplifier
• Vector Generators
For MIL-STD-883 compliant product consult the
HA-2556/883 datasheet.
Ordering Information
Functional Block Diagram
TEMP.
PKG.
NO.
o
PART NUMBER RANGE ( C)
PACKAGE
16 Ld PDIP
HA-2556
V +
X
V
OUT
HA3-2556-9
HA9P2556-9
HA1-2556-9
-40 to 85
-40 to 85
-40 to 85
E16.3
+
A
-
X
Y
V -
X
16 Ld SOIC
M16.3
F16.3
16 Ld CERDIP
+
∑
1/SF
Pinout
-
HA-2556
(PDIP, CERDIP, SOIC)
V +
V +
Y
Z
Z
+
-
+
-
TOP VIEW
V -
V -
Z
Y
GND
1
2
3
4
5
6
7
8
16 V
15 V
A
XIO
REF
V
B
XIO
NOTE: The transfer equation for the HA-2556 is:
REF
(V -V ) (V -V ) = S (V -V ),
X+ X- Y+ Y- Z+ Z-
F
V
B
14 NC
13 V +
YIO
where SF = Scale Factor = 5V; V
V
X, Y,
V
A
YIO
X
V
= Differential Inputs.
Z
X
Z
V +
12 V -
X
Y
Y
V
-
11 V+
Y
+
Σ
10 V -
Z
V-
-
9
V +
Z
V
OUT
CAUTION: These devices are sensitive to electrostatic discharge; follow proper IC Handling Procedures.
1-888-INTERSIL or 321-724-7143 | Copyright © Intersil Corporation 1999
1
HA-2556
Absolute Maximum Ratings
Thermal Information
o
o
Voltage Between V+ and V- Terminals. . . . . . . . . . . . . . . . . . . . 35V
Differential Input Voltage . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 6V
Output Current . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . ±60mA
Thermal Resistance (Typical, Note 1)
PDIP Package . . . . . . . . . . . . . . . . . . .
SOIC Package . . . . . . . . . . . . . . . . . . .
CERDIP Package. . . . . . . . . . . . . . . . .
θ
( C/W)
θ
( C/W)
JA
JC
77
90
75
N/A
N/A
20
o
Maximum Junction Temperature (Ceramic Package) . . . . . . . 175 C
Maximum Junction Temperature (Plastic Packages) . . . . . . 150 C
Maximum Storage Temperature Range. . . . . . . . . . -65 C to 150 C
Maximum Lead Temperature (Soldering 10s) . . . . . . . . . . . . 300 C
Operating Conditions
o
o
o
Temperature Range . . . . . . . . . . . . . . . . . . . . . . . . . -40 C to 85 C
o
o
o
(SOIC - Lead Tips Only)
CAUTION: Stresses above those listed in “Absolute Maximum Ratings” may cause permanent damage to the device. This is a stress only rating and operation of the
device at these or any other conditions above those indicated in the operational sections of this specification is not implied.
NOTE:
1. θ is measured with the component mounted on an evaluation PC board in free air.
JA
Electrical Specifications
PARAMETER
V
= ±15V, R = 50Ω, R = 1kΩ, C = 20pF, Unless Otherwise Specified
SUPPLY F L L
o
TEST CONDITIONS
TEMP. ( C)
MIN
TYP
MAX
UNITS
MULTIPLIER PERFORMANCE
Transfer Function
(V – V ) × (V – V
)
X+
X-
Y+
Y-
V
= A -------------------------------------------------------------------- – (V – V
)
OUT
Z+
Z-
5
Multiplication Error
Note 2
25
Full
Full
25
-
-
-
-
-
-
-
1.5
3.0
3
%
%
6
o
Multiplication Error Drift
Scale Factor
0.003
5
-
-
%/ C
V
Linearity Error
V , V = ±3V, Full Scale = 3V
25
0.02
0.05
0.2
-
%
%
%
X
Y
V , V = ±4V, Full Scale = 4V
25
0.25
0.5
X
Y
V , V = ±5V, Full Scale = 5V
25
X
Y
AC CHARACTERISTICS
Small Signal Bandwidth (-3dB)
V
V
= 200mV
= 200mV
, V = 5V
25
25
25
25
25
25
25
25
25
25
25
25
25
25
-
57
52
-
MHz
MHz
MHz
V/µs
ns
Y
X
P-P
X
, V = 5V
-
-
P-P
Y
Full Power Bandwidth (-3dB)
Slew Rate
10V
-
32
-
P-P
Note 5
Note 6
Note 6
420
450
8
-
Rise Time
-
-
Overshoot
-
20
-
%
Settling Time
To 0.1%, Note 5
Notes 3, 8
-
100
0.1
0.1
5.0
4.0
0.03
-65
-50
-
ns
Differential Gain
Differential Phase
-
0.2
%
Notes 3, 8
-
4.0
2.0
-
0.3
Degrees
MHz
MHz
%
V
V
0.1dB Gain Flatness
0.1dB Gain Flatness
200mV
200mV
Note 4
200mV
200mV
, V = 5V, Note 8
-
-
-
-
-
Y
X
P-P
X
, V = 5V, Note 8
Y
P-P
THD + N
1MHz Feedthrough
5MHz Feedthrough
, Other Ch Nulled
, Other Ch Nulled
-
dB
P-P
-
dB
P-P
SIGNAL INPUT (V , V , V
Z)
X
Y
Input Offset Voltage
25
Full
Full
25
-
-
-
-
-
3
8
15
25
-
mV
mV
o
Average Offset Voltage Drift
Input Bias Current
45
8
µV/ C
15
20
µA
µA
Full
12
2
HA-2556
Electrical Specifications
PARAMETER
V
= ±15V, R = 50Ω, R = 1kΩ, C = 20pF, Unless Otherwise Specified (Continued)
SUPPLY
F
L
L
o
TEST CONDITIONS
TEMP. ( C)
MIN
TYP
0.5
1.0
1
MAX
UNITS
µA
Input Offset Current
25
Full
25
-
-
2
3
-
µA
Differential Input Resistance
-
MΩ
V
Full Scale Differential Input (V , V , V )
25
±5
-
-
-
X
Y
Z
V
V
Common Mode Range
Common Mode Range
25
±10
+9, -10
78
-
V
X
Y
25
-
-
V
CMRR Within Common Mode Range
Voltage Noise (Note 9)
Full
25
65
-
-
dB
f = 1kHz
150
40
-
nV/√Hz
nV/√Hz
f = 100kHz
25
-
-
OUTPUT CHARACTERISTICS
Output Voltage Swing
Output Current
Output Resistance
POWER SUPPLY
+PSRR
Note 10
Full
Full
25
±5.0
±20
-
±6.05
±45
-
-
V
mA
Ω
0.7
1.0
Note 7
Note 7
Full
Full
Full
65
45
-
80
55
18
-
-
dB
dB
-PSRR
Supply Current
NOTES:
22
mA
2. Error is percent of full scale, 1% = 50mV.
3. f = 4.43MHz, V = 300mV , 0 to 1V
offset, V = 5V.
Y
P-P
, V = 5V.
DC
X
4. f = 10kHz, V = 1V
Y
RMS
X
5. V
6. V
= 0 to ±4V.
OUT
OUT
= 0 to ±100mV.
7. V = ±12V to ±15V.
S
8. Guaranteed by characterization and not 100% tested.
9. V = V = 0V.
X
Y
10. V = 5.5V, V = ±5.5V.
X
Y
Simplified Schematic
V+
V
BIAS
V
BIAS
V
CC
V +
X
V -
X
V +
V -
Y
Y
OUT
V +
Z
REF
V -
Z
+
-
V
A
YIO
V-
V
A
V
B
V
B
YIO
XIO
XIO
GND
3
HA-2556
To accomplish this the differential input voltages are first
Application Information
converted into differential currents by the X and Y input
transconductance stages. The currents are then scaled by a
constant reference and combined in the multiplier core. The
multiplier core is a basic Gilbert Cell that produces a
differential output current proportional to the product of X and
Y input signal currents. This current becomes the output for
the HA-2557.
Operation at Reduced Supply Voltages
The HA-2556 will operate over a range of supply voltages,
±5V to ±15V. Use of supply voltages below ±12V will reduce
input and output voltage ranges. See “Typical Performance
Curves” for more information.
Offset Adjustment
The HA-2556 takes the output current of the core and feeds it
to a transimpedance amplifier, that converts the current to a
voltage. In the multiplier configuration, negative feedback is
provided with the Z transconductance amplifier by connecting
X and Y channel offset voltages may be nulled by using a
20K potentiometer between the V
or V
adjust pin A
YIO
XIO
and B and connecting the wiper to V-. Reducing the channel
offset voltage will reduce AC feedthrough and improve the
multiplication error. Output offset voltage can also be nulled
V
to the Z input. The Z stage converts V to a current
OUT
OUT
which is subtracted from the multiplier core before being
applied to the high gain transimpedance amp. The Z stage, by
virtue of it’s similarity to the X and Y stages, also cancels
by connecting V - to the wiper of a potentiometer which is
tied between V+ and V-.
Z
Capacitive Drive Capability
second order errors introduced by the dependence of V on
BE
When driving capacitive loads >20pF a 50Ω resistor should
collector current in the X and Y stages.
be connected between V
and V +, using V + as the
OUT
Z Z
The purpose of the reference circuit is to provide a stable
current, used in setting the scale factor to 5V. This is
achieved with a bandgap reference circuit to produce a
temperature stable voltage of 1.2V which is forced across a
NiCr resistor. Slight adjustments to scale factor may be
output (see Figure 1). This will prevent the multiplier from
going unstable and reduce gain peaking at high frequencies.
The 50Ω resistor will dampen the resonance formed with the
capacitive load and the inductance of the output at pin 8.
Gain accuracy will be maintained because the resistor is
inside the feedback loop.
possible by overriding the internal reference with the V
REF
pin. The scale factor is used to maintain the output of the
multiplier within the normal operating range of ±5V when
full scale inputs are applied.
Theory of Operation
The HA-2556 creates an output voltage that is the product
of the X and Y input voltages divided by a constant scale
factor of 5V. The resulting output has the correct polarity in
each of the four quadrants defined by the combinations of
positive and negative X and Y inputs. The Z stage provides
the means for negative feedback (in the multiplier
configuration) and an input for summation into the output.
This results in the following equation, where X, Y and Z are
high impedance differential inputs.
The Balance Concept
The open loop transfer equation for the HA-2556 is:
(V -V ) x (V
–V )
Y-
X+
X-
Y+
------------------------------------------------------------------
- (V -V )
Z+ Z-
V
= A
OUT
5V
where;
A
= Output Amplifier Open Loop Gain
= Differential Input Voltages
= Fixed Scaled Factor
V
V
V
Z
X, Y,
5V
1
2
3
4
5
6
7
8
16
15
14
13
12
11
10
9
NC
NC
NC
REF
NC
NC
NC
An understanding of the transfer function can be gained by
assuming that the open loop gain, A, of the output amplifier
is infinite. With this assumption, any value of V
generated with an infinitesimally small value for the terms
within the brackets. Therefore we can write the equation:
V +
X
+
-
can be
OUT
V +
Y
+
-
+15 V
V -
Z
+
Σ
-
-15V
-
+
(V -V ) x (V -V )
Y-
X+
X-
Y+
----------------------------------------------------------------
0 =
- (V -V )
Z+ Z-
V +
V
Z
OUT
5V
50Ω
20pF
1kΩ
which simplifies to:
(V -V ) x (V -V ) = 5V (V -V )
Z-
X+
X-
Y+
Y-
Z+
FIGURE 1. DRIVING CAPACITIVE LOAD
This form of the transfer equation provides a useful tool to
analyze multiplier application circuits and will be called the
Balance Concept.
X x Y
-------------
5
V
= Z =
OUT
4
HA-2556
Here the Balance equation will appear as:
Typical Applications
Let’s first examine the Balance Concept as it applies to the
standard multiplier configuration (Figure 2).
(A) x (A) = 5(W)
V +
X
HA-2556
V
OUT
A
+
A
HA-2556
W
V +
X
-
V
X
Y
OUT
V -
X
A
+
A
W
-
+
X
Y
V -
X
1/5V
∑
+
-
V +
Y
V +
Z
1/5V
∑
Z
B
+
-
+
-
-
V +
Y
V +
Z
Z
V -
Y
V -
Z
+
-
+
-
V -
Y
V -
Z
FIGURE 2. MULTIPLIER
FIGURE 4. SQUARE
Signals A and B are input to the multiplier and the signal W
is the result. By substituting the signal values into the
Balance equation you get:
Which simplifies to:
(A) x (B) = 5(W)
2
A
W = ------
And solving for W:
A x B
5
-------------
W =
The last basic configuration is the Square Root as shown in
Figure 5. Here feedback is provided to both X and Y inputs.
5
Notice that the output (W) enters the equation in the
feedback to the Z stage. The Balance Equation does not test
for stability, so remember that you must provide negative
feedback. In the multiplier configuration, the feedback path is
HA-2556
V +
X
V
OUT
+
W
A
-
X
Y
V -
X
connected to V + input, not V -. This is due to the inversion
Z
Z
+
1/5V
∑
that takes place at the summing node just prior to the output
amplifier. Feedback is not restricted to the Z stage, other
feedback paths are possible as in the Divider Configuration
shown in Figure 3.
-
V +
Y
V +
Z
Z
+
-
+
-
A
V -
Y
V -
Z
FIGURE 5. SQUARE ROOT (FOR A > 0)
HA-2556
V +
X
V
OUT
+
A
W
-
The Balance equation takes the form:
X
Y
V -
X
+
(W) × (–W) = 5(–A)
1/5V
∑
-
V +
Y
V +
Z
Z
B
+
-
+
-
Which equates to:
A
V -
Y
V -
Z
W = 5A
FIGURE 3. DIVIDER
The four basic configurations (Multiply, Divide, Square and
Square Root) as well as variations of these basic circuits
have many uses.
Inserting the signal values A, B and W into the Balance
Equation for the divider configuration yields:
(-W) (B) = 5V x (-A)
Frequency Doubler
For example, if ACos(ωτ) is substituted for signal A in the
Square function, then it becomes a Frequency Doubler and
the equation takes the form:
Solving for W yields:
5A
------
W =
B
Notice that, in the divider configuration, signal B must remain
(ACos(ωτ)) × (ACos(ωτ)) = 5(W)
≥0 (positive) for the feedback to be negative. If signal B is
And using some trigonometric identities gives the result:
negative, then it will be multiplied by the V input to produce
X-
positive feedback and the output will swing into the rail.
2
A
------
W =
(1 + Cos(2ωτ))
10
Signals may be applied to more than one input at a time as
in the Squaring configuration in Figure 4:
5
HA-2556
input was dedicated to a slow moving control function as is
required for Automatic Gain Control. The HA-2556 is
versatile enough for both.
Square Root
The Square Root function can serve as a precision/wide
bandwidth compander for audio or video applications. A
compander improves the Signal to Noise Ratio for your
Although the X and Y inputs have similar AC characteristics,
they are not the same. The designer should consider input
parameters such as small signal bandwidth, AC feedthrough
and 0.1dB gain flatness to get the most performance from
the HA-2556. The Y channel is the faster of the two inputs
with a small signal bandwidth of typically 57MHz versus
52MHz for the X channel. Therefore in AM Signal
system by amplifying low level signals while attenuating or
0.5
compressing large signals (refer to Figure 17; X
curve).
This provides for better low level signal immunity to noise
during transmission. On the receiving end the original signal
may be reconstructed with the standard Square function.
Communications
Generation, the best performance will be obtained with the
Carrier applied to the Y channel and the modulation signal
(lower frequency) applied to the X channel.
The Multiplier configuration has applications in AM Signal
Generation, Synchronous AM Detection and Phase
Detection to mention a few. These circuit configurations are
shown in Figures 6, 7 and 8. The HA-2556 is particularly
useful in applications that require high speed signals on all
inputs.
Scale Factor Control
The HA-2556 is able to operate over a wide supply voltage
range ±5V to ±17.5V. The ±5V range is particularly useful in
video applications. At ±5V the input voltage range is reduced
to ±1.4V. The output cannot reach its full scale value with this
restricted input, so it may become necessary to modify the
scale factor. Adjusting the scale factor may also be useful
when the input signal itself is restricted to a small portion of
the full scale level. Here we can make use of the high gain
output amplifier by adding external gain resistors.
V +
ACos(ω τ)
X
HA-2556
Α
V
OUT
+
-
A
W
Audio
X
Y
V -
X
+
1/5V
∑
-
V +
Y
V +
CCos(ω τ)
Z
C
Z
+
-
+
-
Carrier
Generating the maximum output possible for a given input
signal will improve the Signal to Noise Ratio and Dynamic
Range of the system. For example, let’s assume that the
V -
V -
Z
Y
AC
--------
W =
(Cos(ω – ω )τ + Cos(ω + ω )τ)
C A C A
10
FIGURE 6. AM SIGNAL GENERATION
input signals are 1V
each. Then the maximum output
PEAK
for the HA-2556 will be 200mV. (1V x 1V)/(5V) = 200mV. It
would be nice to have the output at the same full scale as
our input, so let’s add a gain of 5 as shown in Figure 9.
V +
X
HA-2556
AM Signal
Carrier
V
OUT
+
W
A
-
X
Y
V -
X
V +
X
HA-2556
+
V
OUT
A
1/5V
∑
+
A
W
-
-
V +
Y
X
Y
V +
Z
V -
X
Z
+
-
+
-
+
1kΩ
1/5V
∑
R
V -
V -
F
Y
Z
-
V +
Y
V +
Z
Z
B
+
-
+
-
LIKE THE FREQUENCY DOUBLER YOU GET AUDIO CENTERED AT DC
250Ω
AND 2F .
V -
Y
V -
Z
C
R
G
R
FIGURE 7. SYNCHRONOUS AM DETECTION
F
ExternalGain = -------- + 1
R
G
HA-2556
V +
X
ACos(ωτ)
FIGURE 9. EXTERNAL GAIN OF 5
V
OUT
+
A
W
-
X
Y
One caveat is that the output bandwidth will also drop by this
factor of 5. The multiplier equation then becomes:
V -
X
+
1/5V
∑
-
5AB
5
V +
Y
V +
ACos(ωτ+φ)
Z
W = ----------- = A × B
Z
+
-
+
-
V -
V -
Z
Y
Current Output
2
A
------
W =
(Cos(φ) + Cos(2ωτ + φ))
10
Another useful circuit for low voltage applications allows the
user to convert the voltage output of the HA2556 to an output
current. The HA-2557 is a current output version offering
100MHz of bandwidth, but its scale factor is fixed and does not
have an output amplifier for additional scaling. Fortunately the
circuit in Figure 10 provides an output current that can be
DC COMPONENT IS PROPORTIONAL TO COS(f)
FIGURE 8. PHASE DETECTION
Each input X, Y and Z has similar wide bandwidth and input
characteristics. This is unlike earlier products where one
6
HA-2556
scaled with the value of R
CONVERT
impedance of typically 1MΩ. The equation for I
and provides an output
becomes:
Of course the HA-2556 is also well suited to standard
multiplier applications such as Automatic Gain Control and
Voltage Controlled Amplifier.
OUT
A × B
5
1
------------- --------------------------------
I
=
×
OUT
R
CONVERT
A
HA-2556
V +
X
2
2
W = 5(A -B )
+
A
Video Fader
The Video Fader circuit provides a unique function. Here Ch B
is applied to the minus Z input in addition to the minus Y input.
In this way, the function in Figure 11 is generated. V
control the percentage of Ch A and Ch B that are mixed
-
X
Y
V -
X
5K
5K
+
5K
5K
1/5V
∑
V +
Y
V +
-
B
Z
Z
will
+
-
+
-
MIX
V -
V -
Z
Y
together to produce a resulting video image or other signal.
FIGURE 12. DIFFERENCE OF SQUARES
95K
HA-2556
V +
V
R
CONVERT
X
OUT
A
+
A
I
OUT
-
X
Y
V -
X
HA-2556
R
5K
R
2
A - B
A
1
+
V -
V
W = 100
X
OUT
1/5V
∑
+
-
A
-
V +
Y
V +
X
Y
Z
B
V +
X
Z
+
+
-
+
-
1/5V
∑
-
V +
Y
V -
Y
V -
Z
V +
Z
A
Z
B
+
-
+
-
FIGURE 10. CURRENT OUTPUT
V -
V -
Z
Y
The Balance equation looks like:
R
and R set scale to 1V/%, other scale factors possible.
2
1
For A 0V.
(V
) × (ChA – ChB) = 5(V
– ChB)
OUT
MIX
FIGURE 13. PERCENTAGE DEVIATION
Which simplifies to:
V
HA-2556
MIX
5
A - B
B + A
-------------
V
= ChB +
(ChA – ChB)
V -
V
X
W = 10
OUT
OUT
+
A
-
X
Y
When V
MIX
is 0V the equation becomes V = Ch B and
OUT
V +
X
+
Ch A is removed, conversely when V
is 5V the equation
values
≤ 5V the output is a blend of Ch A and Ch B.
MIX
1/5V
∑
becomes V
0V ≤ V
= Ch A eliminating Ch B. For V
MIX
OUT
-
V +
Y
V +
Z
Z
B
A
MIX
+
-
+
-
5K
5K
V -
V -
Z
Y
1
2
3
4
5
6
7
8
16
15
14
13
12
11
10
9
NC
NC
REF
NC
NC
NC
NC
+
MIX
(0V to 5V)
V
X
V
FIGURE 14. DIFFERENCE DIVIDED BY SUM S (For A + B ≥ 0V)
+
Ch A
Ch B
V +
-
Y
+
V -
Y
Automatic Gain Control
-
+15 V
V -
Figure 15 shows the HA-2556 configured in an Automatic
Gain Control or AGC application. The HA-5127 low noise
amplifier provides the gain control signal to the X input. This
control signal sets the peak output voltage of the multiplier to
match the preset reference level. The feedback network
around the HA-5127 provides a response time adjustment.
High frequency changes in the peak are rejected as noise or
the desired signal to be transmitted. These signals do not
indicate a change in the average peak value and therefore
no gain adjustment is needed. Lower frequency changes in
the peak value are given a gain of -1 for feedback to the
control input. At DC the circuit is an integrator automatically
compensating for Offset and other constant error terms.
Z
+
Σ
-15V
-
-
+
V +
Z
V
OUT
50Ω
FIGURE 11. VIDEO FADER
Other Applications
As shown above, a function may contain several different
operators at the same time and use only one HA-2556.
Some other possible multi-operator functions are shown in
Figures 12, 13 and 14.
7
HA-2556
This multiplier has the advantage over other AGC circuits, in
that the signal bandwidth is not affected by the control signal
gain adjustment.
Wave Shaping Circuits
Wave shaping or curve fitting is another class of application
for the analog multiplier. For example, where a nonlinear
sensor requires corrective curve fitting to improve linearity
the HA-2556 can provide nonintegral powers in the range 1
to 2 or nonintegral roots in the range 0.5 to 1.0 (refer to
References). This effect is displayed in Figure 17.
HA-2556
1
2
3
4
5
6
7
8
16
15
14
13
12
11
10
9
NC
NC
NC
REF
NC
NC
NC
1
X
Z
0.5
V +
Y
X
0.8
0.6
0.4
0.2
0
Y
V+
0.7
X
+
Σ
V-
-
V
OUT
1.5
X
50Ω
2
X
10kΩ
0.1µF
1N914
0
0.2
0.4
0.6
0.8
1
0.01µF
10kΩ
+15V
INPUT (V)
-
+
FIGURE 17. EFFECT OF NONINTEGRAL POWERS / ROOTS
5.6V
5kΩ
HA-5127
20kΩ
A multiplier can’t do nonintegral roots “exactly”, but it can
yield a close approximation. We can approximate
nonintegral roots with equations of the form:
2
0.1µF
V
= (1 – α )V + α V
IN
o
IN
FIGURE 15. AUTOMATIC GAIN CONTROL
HA-2556
1 ⁄ 2
V
= (1 – α )V
+ α V
IN IN
o
0.7
Figure 18 compares the function V
0.5
= V
IN
to the
OUT
+ 0.5V .
IN
approximation V
= 0.5V
1
2
3
4
5
6
7
8
16 NC
15 NC
14 NC
OUT
IN
REF
1
NC
NC
NC
0.8
0.6
0.4
0.2
13
12
11
10
9
V
+ (V )
GAIN
0.7
X
X
X
Z
Y
V+
+
Σ
V-
-
0.5
0.5X + 0.5X
X
5kΩ
500Ω
0
0
V
IN
-
0.2
0.4
0.6
0.8
1
+
V
OUT
INPUT (V)
HFA0002
FIGURE 18. COMPARE APPROXIMATION TO NONINTEGRAL
ROOT
FIGURE 16. VOLTAGE CONTROLLED AMPLIFIER
Voltage Controlled Amplifier
This function can be easily built using an HA-2556 and a
potentiometer for easy adjustment as shown in Figures 19 and
20. If a fixed nonintegral power is desired, the circuit shown in
A wide range of gain adjustment is available with the Voltage
Controlled Amplifier configuration shown in Figure 16. Here
the gain of the HFA0002 can be swept from 20V/V to a gain
of almost 1000V/V with a DC voltage from 0V to 5V.
Figure 21 eliminates the need for the output buffer amp. These
M
circuits approximate the function
nonintegral power or root.
where M is the desired
V
IN
8
HA-2556
Values for α to give a desired M root or power are as follows:
HA-2556
ROOTS - FIGURE 19
POWERS - FIGURE 20
1
2
3
4
5
6
7
8
16
NC
REF
M
α
M
α
NC
NC
NC
15 NC
14 NC
13
0.5
0.6
0.7
0.8
0.9
1.0
0
1.0
1.2
1.4
1.6
1.8
2.0
1
+
≈0.25
≈0.50
≈0.70
≈0.85
1
≈0.75
≈0.5
≈0.3
≈0.15
0
X
Z
+
12
-
Y
11
10
9
V+
-
+
+
Σ
V
IN
V-
-
1-α
-
α
Sine Function Generators
Similar functions can be formulated to approximate a SINE
function converter as shown in Figure 22. With a linearly
changing (0V to 5V) input the output will follow 0 degrees to 90
degrees of a sine function (0V to 5V) output. This configuration
is theoretically capable of ±2.1% maximum error to full scale.
V
OUT
-
0.5 ≤ M ≤ 1.0
0V ≤ V ≤ 1V
+
HA-5127
IN
FIGURE 19. NONINTEGRAL ROOTS - ADJUSTABLE
HA-2556
By adding a second HA-2556 to the circuit an improved fit
may be achieved with a theoretical maximum error of ±0.5%
as shown in Figure 23. Figure 23 has the added benefit that it
will work for positive and negative input signals. This makes a
convenient triangle (±5V input) to sine wave (±5V output)
converter.
1
2
3
4
5
6
7
8
16 NC
15 NC
14 NC
13
REF
NC
NC
NC
V
IN
+
X
Z
+
12
-
Y
11 V+
10
References
[1] Pacifico Cofrancesco, “RF Mixers and Modulators made
with a Monolithic Four-Quadrant Multiplier” Microwave
Journal, December 1991 pg. 58 - 70.
-
1-α
+
+
Σ
V-
-
α
9
-
[2] Richard Goller, “IC Generates Nonintegral Roots”
Electronic Design, December 3, 1992.
1.0 ≤ M ≤ 2.0
0V ≤ V ≤ 1V
V
OUT
-
+
IN
HA-5127
HA-2556
FIGURE 20. NONINTEGRAL POWERS - ADJUSTABLE
HA-2556
1
2
3
4
5
6
7
8
16 NC
15 NC
14 NC
13
REF
NC
NC
NC
R
R
2
6
NC
NC
1
2
3
4
5
6
7
8
16
15
470
470
REF
+
NC
NC
NC
V
X
Z
IN
+
14 NC
13
12
V
IN
-
+
Y
R
1
262
11 V+
10
R
5
X
Z
+
-
+
12
1410
+
Σ
-
V-
-
Y
V
OUT
R
R
11
10
9
1
V+
-
9
-
+
+
Σ
V-
-
V
OUT
-
2
R , 644
R , 1K
4
3
1.2 ≤ M ≤ 2.0
0V ≤ V ≤ 1V
R
3
R
FIGURE 22. SINE-FUNCTION GENERATOR
4
IN
FIGURE 21. NONINTEGRAL POWERS - FIXED
R
R
R
3
R
4
1
--
5
2
3
2
--------------------
V
IN
V
=
------ + 1 V
+
------ + 1
OUT
IN
R
+ R
2
R
4
1
Setting:
R
R
R
3
R
4
1
5
2
3
--
--------------------
1 – α =
------ + 1
α = ------ + 1
R
1
+ R
R
4
2
9
HA-2556
(1 – 0.1284V
)
V
π
IN
IN
71.5K
V
23.1K
-------------------------------------------------- -- ---------
≈ 5sin
V
= V
OUT
IN
(0.6082 – 0.05V
)
2
5
IN
+
-
X
for; 0V ≤ V ≤ 5V
Max Theoretical Error = 2.1%FS
V
OUT
IN
X
where:
OUT
V
IN
+
-
10K
R
R
2
5.71K
10K
X
HA-2556
+
;
4
0.6082 = --------------------
5(0.1284) = --------------------
R
+ R
R
+ R
2
+
-
3
4
1
Z
V
OUT
X
Y
R
6
-
5(0.05) = --------------------
HA-2556
Z
Y
R
+ R
5
6
+
-
+
Z
Y
3
5V – 0.05494V
V
IN
5
π
2
IN
IN
-
Z
Y
------------------------------------------------------------------
3.18167 + 0.0177919V
-- ---------
V
=
≈ 5sin
OUT
2
IN
FIGURE 23. BIPOLAR SINE-FUNCTION GENERATOR
for; -5V ≤ V ≤ 5V
IN
Max Theoretical Error = 0.5%FS
Typical Performance Curves
1.5
1
Y = -4
Y = -5
Y = -3
1
0.5
0
0.5
Y = -2
Y = 0
Y = -1
Y = 0
0
Y = 1
-0.5
-1
Y = 3
Y = 2
-0.5
Y = 4
Y = 5
-1
-1.5
-6
-4
-2
0
2
4
6
-6
-4
-2
0
2
4
6
X INPUT (V)
X INPUT (V)
FIGURE 24. X CHANNEL MULTIPLIER ERROR
FIGURE 25. X CHANNEL MULTIPLIER ERROR
1.5
1
1
X = -3
X = -2
0.5
0
X = -4
X = -1
X = 0
X = 5
X = 1
0.5
0
X = 0
-0.5
-1
X = -5
X = 2
-0.5
-1
X = 4
X = 3
-1.5
-6
-4
-2
0
2
4
6
-6
-4
-2
0
2
4
6
Y INPUT (V)
Y INPUT (V)
FIGURE 26. Y CHANNEL MULTIPLIER ERROR
FIGURE 27. Y CHANNEL MULTIPLIER ERROR
10
HA-2556
Typical Performance Curves (Continued)
200
100
8
4
0
0
-100
-200
-4
V
V
= ±100mV PULSE
Y
X
V
V
= ±4V PULSE
X
Y
= 5V
DC
= 5V
DC
-8
0ns
250ns
500ns
0ns
500ns
1µs
50mV/DIV.; 50ns/DIV.
2V/DIV.; 100ns/DIV.
FIGURE 28. LARGE SIGNAL RESPONSE
FIGURE 29. SMALL SIGNAL RESPONSE
Y CHANNEL = 4V
X CHANNEL = 5V
P-P
DC
Y CHANNEL = 10V
P-P
4
3
4
X CHANNEL = 5V
DC
3
2
2
1
1
0
0
-1
-2
-3
-4
-1
-2
-3
-4
-3dB
AT 32.5MHz
10K
100K
1M
10M
10K
100K
1M
FREQUENCY (Hz)
10M
FREQUENCY (Hz)
FIGURE 30. Y CHANNEL FULL POWER BANDWIDTH
FIGURE 31. Y CHANNEL FULL POWER BANDWIDTH
X CHANNEL = 10V
P-P
X CHANNEL = 4V
Y CHANNEL = 5V
4
3
P-P
DC
4
3
Y CHANNEL = 5V
DC
2
2
1
1
0
0
-1
-2
-3
-4
-1
-2
-3
-4
10K
100K
1M
FREQUENCY (Hz)
10M
10K
100K
1M
FREQUENCY (Hz)
10M
FIGURE 32. X CHANNEL FULL POWER BANDWIDTH
FIGURE 33. X CHANNEL FULL POWER BANDWIDTH
11
HA-2556
Typical Performance Curves (Continued)
0
0
-6
V
= 5V
DC
V
= 5V
DC
Y
X
-6
-12
-18
-24
V
= 2V
DC
Y
V
= 2V
DC
X
-12
-18
-24
V
= 0.5V
DC
Y
V
= 200mV
P-P
V
= 0.5V
Y
V = 200mV
X
X
DC
P-P
100M
10K
100K
1M
FREQUENCY (Hz)
10M
10K
100K
1M
FREQUENCY (Hz)
10M
100M
FIGURE 34. Y CHANNEL BANDWIDTH vs X CHANNEL
FIGURE 35. X CHANNEL BANDWIDTH vs Y CHANNEL
0
0
V
V
+, V - = 200mV
Y RMS
Y
X
V
V
+, V - = 200mV
RMS
X
Y
X
-10
-20
-30
-40
-50
-60
-70
-80
-10
-20
-30
-40
-50
-60
-70
-80
= 5V
DC
= 5V
DC
5MHz
-26.2dB
5MHz
-38.8dB
10K
100K
1M
FREQUENCY (Hz)
10M
100M
10K
100K
1M
FREQUENCY (Hz)
10M
100M
FIGURE 36. Y CHANNEL CMRR vs FREQUENCY
FIGURE 37. X CHANNEL CMRR vs FREQUENCY
0
0
V
V
= 200mV
P-P
V
V
= 200mV
X
Y
X
P-P
= NULLED
-10
-10
-20
-30
-40
-50
-60
-70
-80
= NULLED
Y
-20
-30
-40
-50
-60
-70
-80
-49dB
AT 5MHz
-52.6dB
AT 5MHz
10K
100K
1M
10M
100M
10K
100K
1M
10M
100M
FREQUENCY (Hz)
FREQUENCY (Hz)
FIGURE 38. FEEDTHROUGH vs FREQUENCY
FIGURE 39. FEEDTHROUGH vs FREQUENCY
12
HA-2556
Typical Performance Curves (Continued)
14
13
12
11
10
9
8
7
6
|V Z|
IO
5
4
3
2
1
0
8
7
|V X|
IO
6
5
|V Y|
IO
4
-100
-50
0
50
100
150
-100
-50
0
50
100
150
o
o
TEMPERATURE ( C)
TEMPERATURE ( C)
FIGURE 41. INPUT BIAS CURRENT (V , V , V ) vs
FIGURE 40. OFFSET VOLTAGE vs TEMPERATURE
X
Y
Z
TEMPERATURE
2
6
5
4
3
2
1
1.5
1
X INPUT
Y INPUT
0.5
0
-0.5
-1
4
6
8
10
12
14
16
-100
-50
0
50
100
150
o
SUPPLY VOLTAGE (±V)
TEMPERATURE ( C)
FIGURE 42. SCALE FACTOR ERROR vs TEMPERATURE
FIGURE 43. INPUT VOLTAGE RANGE vs SUPPLY VOLTAGE
15
25
20
X INPUT
10
I
Y INPUT
CC
I
5
EE
15
10
5
0
-5
X & Y INPUT
-10
-15
0
0
5
10
15
20
4
6
8
10
12
14
16
SUPPLY VOLTAGE (±V)
SUPPLY VOLTAGE (±V)
FIGURE 45. SUPPLY CURRENT vs SUPPLY VOLTAGE
FIGURE 44. INPUT COMMON MODE RANGE vs SUPPLY
VOLTAGE
13
HA-2556
Typical Performance Curves (Continued)
5.0
4.8
4.6
4.4
4.2
100
300
500
700
900
1100
R
(Ω)
LOAD
FIGURE 46. OUTPUT VOLTAGE vs R
LOAD
Die Characteristics
DIE DIMENSIONS:
PASSIVATION:
Type: Nitride (Si N ) over Silox (SiO , 5% Phos)
71 mils x 100 mils x 19 mils
3
4
2
Silox Thickness: 12kÅ ±2kÅ
Nitride Thickness: 3.5kÅ ±2kÅ
METALLIZATION:
Type: Al, 1% Cu
TRANSISTOR COUNT:
Thickness: 16kÅ ±2kÅ
84
SUBSTRATE POTENTIAL:
V-
HA-2556
Metallization Mask Layout
V
A
V
B
VREF GND
(2) (1)
XIO
(16)
XIO
(15)
V
V
B
YIO
(3)
A
YIO
(4)
V +
X
(13)
V +
Y
(5)
V -
X
(12)
V -
Y
(6)
V+
(11)
(8)
(9) (10)
V + V -
(7)
V-
V
OUT
Z
Z
14
HA-2556
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Intersil semiconductor products are sold by description only. Intersil Corporation reserves the right to make changes in circuit design and/or specifications at any time with-
out notice. Accordingly, the reader is cautioned to verify that data sheets are current before placing orders. Information furnished by Intersil is believed to be accurate and
reliable. However, no responsibility is assumed by Intersil or its subsidiaries for its use; nor for any infringements of patents or other rights of third parties which may result
from its use. No license is granted by implication or otherwise under any patent or patent rights of Intersil or its subsidiaries.
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15
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