HSP43220_04 [INTERSIL]
Decimating Digital Filter; 抽取数字滤波器
| 型号： | HSP43220_04 |
| 厂家： | 
Intersil |
| 描述： | Decimating Digital Filter |
| 文件： | 总18页 (文件大小：806K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
HSP43220
®
Data Sheet
J uly 2004
FN2486.9
Decimating Digital Filter
Features
The HSP43220 Decimating Digital Filter is a linear phase
low pass decimation filter which is optimized for filtering
narrow band signals in a broad spectrum of a signal
processing applications. The HSP43220 offers a single chip
solution to signal processing applications which have
historically required several boards of ICs. This reduction in
component count results in faster development times as well
as reduction of hardware costs.
• Single Chip Narrow Band Filter with up to 96dB
Attenuation
• DC to 33MHz Clock Rate
• 16-Bit 2’s Complement Input
• 20-Bit Coefficients in FIR
• 24-Bit Extended Precision Output
• Programmable Decimation up to a Maximum of 16,384
• Standard 16-Bit Microprocessor Interface
• Filter Design Software Available DECIMATE™
• Up to 512 Taps
The HSP43220 is implemented as a two stage filter
structure. As seen in the block diagram, the first stage is a
high order decimation filter (HDF) which utilizes an efficient
sample rate reduction technique to obtain decimation up to
1024 through a coarse low-pass filtering process. The HDF
provides up to 96dB aliasing rejection in the signal pass
band. The second stage consists of a finite impulse
response (FIR) decimation filter structured as a transversal
FIR filter with up to 512 symmetric taps which can implement
filters with sharp transition regions. The FIR can perform
further decimation by up to 16 if required while preserving
the 96dB aliasing attenuation obtained by the HDF. The
combined total decimation capability is 16,384.
Applications
• Very Narrow Band Filters
• Zoom Spectral Analysis
• Channelized Receivers
• Large Sample Rate Converter
The HSP43220 accepts 16-bit parallel data in 2’s
complement format at sampling rates up to 33MSPS. It
provides a 16-bit microprocessor compatible interface to
simplify the task of programming and three-state outputs to
allow the connection of several ICs to a common bus. The
HSP43220 also provides the capability to bypass either the
HDF or the FIR for additional flexibility.
Ordering Information
TEMP.
PKG.
DWG. #
PART NUMBER
HSP43220JC-25
HSP43220JC-33
RANGE (°C)
PACKAGE
84 Ld PLCC
84 Ld PLCC
0 to 0
N84.1.15
N84.1.15
0 to 70
DECIMATE Software Development Tool (This software tool may be
downloaded from our Internet site: www.intersil.com)
Block Diagram
DECIMATION UP TO 1024
DECIMATION UP TO 16
INPUT CLOCK
24
HIGH ORDER
DECIMATION
FILTER
FIR
DECIMATION
FILTER
16
16
DATA OUT
DATA INPUT
DATA READY
CONTROL AND COEFFICIENTS
FIR CLOCK
CAUTION: These devices are sensitive to electrostatic discharge; follow proper IC Handling Procedures.
1-888-INTERSIL or 321-724-7143 | Intersil (and design) is a registered trademark of Intersil Americas Inc.
Copyright © Intersil Americas Inc. 2000, 2004. All Rights Reserved
1
DECIMATE™ is a trademark of Intersil Corporation.
HSP43220
Pinout
84 PLASTIC LEADED CHIP CARRIER (PLCC)
11 10 9
8 7 6 5 4 3 2 1 84 83 82 81 80 79 78 77 76 75
12
13
14
15
16
17
18
19
20
21
22
23
24
25
26
27
28
29
30
31
32
74
73
72
71
70
69
68
67
66
65
64
63
62
61
60
59
58
57
56
55
54
STARTOUT
GND
V
DATA_OUT 0
DATA_OUT 1
DATA_OUT 2
DATA_OUT 3
DATA_OUT 4
DATA_OUT 5
DATA_OUT 6
DATA_OUT 7
DATA_OUT 8
DATA_OUT 9
DATA_OUT 10
DATA_OUT 11
GND
CC
STARTIN
ASTARTIN
RESET
A1
A0
WR
CS
C_BUS 15
C_BUS 14
C_BUS 13
C_BUS 12
C_BUS 11
C_BUS 10
C_BUS 9
V
CC
DATA_OUT 12
DATA_OUT 13
DATA_OUT 14
DATA_OUT 15
DATA_OUT 16
DATA_OUT 17
V
CC
GND
C_BUS 8
C_BUS 7
C_BUS 6
33 34 35 36 37 38 39 40 41 42 43 44 45 46 47 48 49 50 51 52 53
Pin Des cription
NAME
TYPE
DESCRIPTION
V
The +5V power supply pins.
The device ground.
CC
GND
CK_IN
I
Input Sample Clock. Operations in the HDF are synchronous with the rising edge of this clock signal. The maximum clock
frequency is 33MHz. CK_IN is synchronous with FIR_CK and thus the two clocks may be tied together if required, or CK_IN
can be divided down from FIR_CK. CK_IN is a CMOS level signal.
FIR_CK
I
I
Input Clock for the FIR Filter. This clock must be synchronous with CK_IN. Operations in the FIR are synchronous with the
rising edge of this clock signal. The maximum clock frequency is 33MHz. FIR_CK is a CMOS level signal.
DATA_IN0-
15
Input Data Bus. This bus is used to provide the 16-bit input data to the HSP43220. The data must be provided in a synchro-
nous fashion, and is latched on the rising edge of the CK_IN signal. The data bus is in 2's complement fractional format. Bit
15 is the MSB.
C_BUS0-15
I
Control Input Bus. This input bus is used to load all the filter parameters. The pins WR, CS and A0, A1 are used to select
the destination of the data on the Control bus and write the Control bus data into the appropriate register as selected by A0
and A1
DATA_OUT
0-23
O
Output Data Bus. This 24-Bit output port is used to provide the filtered result in 2's complement format. The upper 8 bits of
the output, DATA_OUT16-23 will provide extension or growth bits depending on the state of OUT_SELH and whether the
FIR has been put in bypass mode. Output bits DATA_OUT0-15 will provide bits 20 through 2-15 when the FIR is not by-
passed and will provide the bits 2-16 through 2-31 when the FIR is in bypass mode.
DATA_RDY
O
An active high output strobe that is synchronous with FIR_CK that indicates that the result of the just completed FIR cycle
is available on the data bus.
2
HSP43220
Pin Des cription (Continued)
NAME
TYPE
DESCRIPTION
RESET
I
RESET is an asynchronous signal which requires that the input clocks CK_IN and FIR_CK are active when RESET is as-
serted. RESET disables the clock divider and clears all of the internal data registers in the HDF. The FIR filter data path is
not initialized. The control register bits that are cleared are F_BYP, H_STAGES, and H_DRATE. The F_DIS bit is set. In
order to guarantee consistent operation of the part, the user must reset the DDF after power up.
WR
CS
I
I
Write Strobe. WR is used for loading the internal registers of the HSP43220. When CS and WR are asserted, the rising edge of
WR will latch the C_BUS0-15 data into the register specified by A0 and A1.
Chip Select. The Chip Select input enables loading of the internal registers. When CS and WR are low, the A0 and A1 address
lines are decoded to determine the destination of the data on C_BUS0-15. The rising edge of WR then loads the appropriate reg-
ister as specified by A0 and A1.
A0, A1
I
I
Control Register Address. These lines are decoded to determine which control register is the destination for the data on
C_BUS0-15. Register loading is controlled by the A0 and A1, WR and CS inputs.
ASTARTIN
STARTOUT
ASTARTIN is an asynchronous signal which is sampled on the rising edge of CK_IN. It is used to put the DDF in operational
mode. ASTARTIN is internally synchronized to CK_IN and is used to generate STARTOUT.
O
STARTOUT is a pulse generated from the internally synchronized version of ASTARTIN. It is provided as an output for use
in multi-chip configurations to synchronously start multiple HSP43220's. The width of STARTOUT is equal to the period of
CK_IN.
STARTIN
I
I
STARTIN is a Synchronous Input. A high to low transition of this signal is required to start the part. STARTIN is sampled on
the rising edge of CK_IN. This synchronous signal can be used to start single or multiple HSP43220's.
OUT_SELH
Output Select. The OUT_SELH input controls which bits are provided at output pins DATA_OUT16-23. A HIGH on this control
line selects bits 28 through 21 from the accumulator output. A LOW on this control line selects bits 2-16 through 2-23 from
the accumulator output. Processing is not interrupted by this pin.
OUT_ENP
OUT_ENX
I
I
Output Enable. The OUT_ENP input controls the state of the lower 16 bits of the output data bus, DATA_OUT0-15. A LOW on
this control line enables the lower 16 bits of the output bus. When OUT_ENP is HIGH, the output drivers are in the high imped-
ance state. Processing is not interrupted by this pin.
Output Enable. The OUT_ENX input controls the state of the upper 8 bits of the output data bus, DATA_OUT16-23. A LOW
on this control line enables the upper 8 bits of the output bus. When OUT_ENX is HIGH, the output drivers are in the high
impedance state. Processing is not interrupted by this pin.
The HDF
Integrator Section
The first filter section is called the High Order Decimation Filter
(HDF) and is optimized to perform decimation by large factors.
It implements a low pass filter using only adders and delay
elements instead of a large number of multiplier/ accumulators
that would be required using a standard FIR filter.
The data from the shifter goes to the Integrator section.
This is a cascade of 5 integrator (or accumulator) stages,
which implement a low pass filter. Each accumulator is
implemented as an adder followed by a register in the feed
forward path. The integrator is clocked by the sample clock,
CK_IN as shown in Figure 2. The bit width of each integrator
stage goes from 66 bits at the first integrator down to 26 bits
at the output of the fifth integrator. Bit truncation is performed
at each integrator stage because the data in the integrator
stages is being accumulated and thus is growing, therefore
the lower bits become insignificant, and can be truncated
without losing significant data.
The HDF is divided into 4 sections: the HDF filter section,
the clock divider, the control register logic and the start logic
(Figure 1).
Data Shifter
After being latched into the Input Register the data enters the
Data Shifter. The data is positioned at the output of the shifter
to prevent errors due to overflow occurring at the output of the
HDF. The number of bits to shift is controlled by H_GROWTH.
3
HSP43220
A0-1
WR CS C_BUS
CK_IN
RESET
RESET CK_IN ASTARTIN
STARTIN
H_DRATE
H_BYP
ISTART
STARTOUT
CONTROL
REGISTER LOGIC
CLOCK
DIVIDER
START
LOGIC
6
5
5
CK DEC
H_GROWTH INT_EN1-5 COMB_EN1-5
HDF FILTER SECTION
ISTART
H_GROWTH
6
INT_EN1-5
5
RESET
COMB_EN1-5
RESET
5
TO FIR
16
INPUT
REG
DATA
SHIFTER
DEC
REG
26
DATA
IN
INTEGRATOR
COMB FILTER
ROUND
REG
16
16
66
26
16
19
CK_IN
TO FIR
CK_DEC
FIGURE 1. HIGH ORDER DECIMATION FILTER FIGURE
0
0
0
0
0
MUX
MUX
MUX
MUX
MUX
TO
INT_EN5
INT_EN4
INT_EN3
INT_EN2
INT_EN1
FROM
SHIFTER
DECIMATION
REGISTER
REG
REG
REG
REG
REG
∑
∑
∑
∑
∑
66
63
53
43
35
26
CK IN
FIGURE 2. INTEGRATOR
There are three signals that control the integrator section;
they are H_STAGES, H_BYP and RESET. In Figure 2 these
control signals have been decoded and are labelled
INT_EN1 - INT_EN5. The order of the filter is loaded via the
control bus and is called H_STAGES. H_STAGES is
decoded to provide the enables for each integrator stage.
When a given integrator stage is selected, the feedback path
is enabled and the integrator accumulates the current data
sample with the previous sum. The integrator section can be
put in bypass mode by the H_BYP bit. When H_BYP or
RESET is asserted, the feedback paths in all integrator
stages are cleared.
Comb Filter Section
The output of the Decimation Register is passed to the
Comb Filter Section. The Comb section consists of 5
cascaded Comb filters or differentiators. Each Comb filter
section calculates the difference between the current and
previous integrator output. Each Comb filter consists of a
register which is clocked by CK_DEC, followed by an
subtractor, where the subtractor calculates the difference
between the input and output of the register. Bit truncations
are done at each stage as shown in Figure 3. The first
stage bit width is 26 bits and the output of the fifth stage is
19 bits.
Decimation Regis ter
There are three signals that control the Comb Filter; H_
STAGES, H_BYP and RESET. In Figure 3 these control
signals are decoded as COMB_EN1 - COMB_EN5. The
order of the Comb filter is controlled by H_STAGES, which is
programmed over the control bus. H_BYP is used to put the
comb section in bypass mode. RESET causes the register
output in each Comb stage to be cleared. The H_ BYP and
RESET control pins, when asserted force the output of all
registers to zero so data is passed through the subtractor
unaltered. When the H_STAGES control bits enable a given
stage the output of the register is subtracted from the input.
The output of the Integrator section is latched into the
Decimation Register by CK_DEC. The output of the
Decimation register is cleared when RESET is asserted. The
HDF decimation rate = H_DRATE +1, which is defined as
H
for convenience.
DEC
4
HSP43220
COMB_EN5
COMB_EN4
COMB_EN3
COMB_EN2
COMB_EN1
FROM
DECI-
MATION
REGISTER
TO
ROUNDER
RESET
REG
RESET
REG
RESET
RESET
REG
RESET
REG
B A-B
A
B A-B
A
REG
B A-B
A
B A-B
A
B A-B
A
19
26
22
21
20
19
CK_DEC
FIGURE 3. COMB FILTER
It is important to note that the Comb filter section has a speed
limitation. The Input sampling rate divided by the decimation
Clock Divider and Control Logic
The clock divider divides CK_IN by the decimation factor
to produce CK_DEC. CK_DEC clocks the Decimation
factor in the HDF (CK_IN/H
) should not exceed 4MHz.
DEC
H
DEC
Violating this condition causes the output of the filter to be
incorrect. When the HDF is put in bypass mode this limitation
does not apply. Equation 1 describes the relationship between
F_TAPS, F_DRATE, H_DRATE, CK_IN and FIR_CK.
Register, Comb Filter section, HDF output register. In the
FIR filter CK_DEC is used to indicate that a new data
sample is available for processing. The clock generator is
cleared by RESET and is not enabled until the DDF is
started by an internal start signal (see Start Logic).
Rounder
The filter accuracy is limited by the 16-bit data input. To
maintain the maximum accuracy, the output of the comb is
rounded to 16 bits.
The Control Register Logic enables the updating of the Control
registers which contain all of the filter parameter data. When
WR and CS are asserted, the control register addressed by bits
A0 and A1 is loaded with the data on the C_BUS.
The Rounder performs a symmetric round of the 19-bit
output of the last Comb stage. Symmetric rounding is done
to prevent the synthesis of a 0Hz spectral component by the
rounding process and thus causing a reduction in spurious
free dynamic range. Saturation logic is also provided to
prevent roll over from the largest positive value to the most
negative value after rounding. The output of the last comb
filter stage in the HDF section has a 16-bit integer portion
with a 3-bit fractional part in 2's complement format.
The rounding algorithm is as follows:
POSITIVE NUMBERS
Fractional Portion Greater Than or Equal to 0.5
Fractional Portion Less Than 0.5
Round Up
Truncate
NEGATIVE NUMBERS
Fractional Portion Less Than or Equal to 0.5
Fractional Portion Greater Than 0.5
Round Up
Truncate
The output of the rounder is latched into the HDF output
register with CK_DEC. CK_DEC is generated by the Clock
Divider section. The output of the register is cleared when
RESET is asserted.
5
HSP43220
DDF Control Regis ters
F_Register (A1 = 0, A0 = 0)
F_OAD
F_BYP F_ESYM
FB0 ES0
14 13
F_DRATE
F_TAPS
FA0
D3 D2 D1 D0 T8 T7 T6 T5 T4 T3 T2 T1 T0
12 11 10
15
9
8
7
6
5
4
3
2
1
0
F_TAPS
Bits T0-T8 are used to specify the number of FIR filter taps. The number
entered is one less than the number of taps required. For example, to
specify a 511 tap filter F_TAPS would be programmed to 510. The mini-
mum number of FIR taps = 3 (F_TAPS = 2).
F_DRATE
Bits D0-D3 are used to specify the amount of FIR decimation. The num-
ber entered is one less than the decimation required. For example, to
specify decimation of 16, F_DRATE would be programmed to 15. For no
FIR decimation, F_DRATE would be set equal to 0. FDRATE +1 is
defined as F
.
DEC
F_ESYM
Bit ES0 is used to select the FIR symmetry. F_ESYM is set equal to one
to select even symmetry and set equal to zero to select odd symmetry.
When F_ESYM is one, data is added in the pre-adder; when it is zero,
data is subtracted. Normally set to one.
F_BYP
FB0 is used to select FIR bypass mode. FIR bypass mode is selected by
setting F_BYP = 1. When FIR bypass mode is selected, the FIR is inter-
nally set up for a 3 tap even symmetric filter, no decimation (F_DRATE =
0) and F_OAD is set equal to one to zero one side of the preadder. In FIR
bypass mode all FIR filter parameters, except F_CLA, are ignored, includ-
ing the contents of the FIR coefficient RAM. In FIR bypass mode the out-
put data is brought output on the lower 16 bits of the output bus
DATA_OUT 0-15. To disable FIR bypass mode, F_BYP is set equal to
zero. When F_BYP is returned to zero, the coefficients must be reloaded.
F_OAD
Bit FA0 is used to select the zero the preadder mode. This mode zeros
one of the inputs to the pre-adder. Zero preadder mode is selected by
setting F_OAD equal to one. This feature is useful when implementing
arbitrary phase filters or can be used to verify the filter coefficients. To
disable the Zero Preadder mode F_OAD is set equal to zero.
FIGURE 4.
6
HSP43220
DDF Control Regis ters (Continued)
FC_Register (A1 = 0, A0 = 1)
F_CF
C19 C18 C17 C16 C15 C14 C13 C12 C11 C10 C9 C8 C7 C6 C5 C4
X
X
X
X
X
X
X
X
X
X
X
X
C3 C2 C1 C0
15
14
13
12
11
10
9
8
7
6
5
4
3
2
1
0
F_CF
Bits C0-C19 represent the coefficient data, where C19 is the MSB. Two writes are
required to write each coefficient which is 2's complement fractional format. The first
write loads C19 through C4; C3 through C0 are loaded on the second write cycle. As
the coefficients are written into this register they are formatted into a 20-bit coefficient
and written into the Coefficient RAM sequentially starting with address location zero.
The coefficients must be loaded sequentially, with the center tap being the last coeffi-
cient to be loaded. See coefficient RAM, below.
FIGURE 5.
H_Register 1 (A1 = 1, A0 = 0)
RESERVED
F_DIS F_CLA H_BYP
FD0 FC0 HB0
H_DRATE
R9 R8 R7 R6 R5 R4 R3 R2 R1 R0
15 14 13
12
11
10
9
8
7
6
5
4
3
2
1
0
H_DRATE Bits
R0-R9 are used to select the amount of decimation in the HDF. The amount of
decimation selected is programmed as the required decimation minus one; for
instance to select decimation of 1024 H_DRATE is set equal to 1023. HDRATE +1 is
defined as H
.
DEC
H_BYP
Bit HB0 is used to select HDF bypass mode. This mode is selected by setting H_BYP =
1. When this mode is selected the input data passes through the HDF unfiltered.
Internally H_STAGES and H_DRATE are both set to zero and H_GROWTH is set to 50.
H_REGISTER 2 must be reloaded when H_BYP is returned to 0. To disable HDF
bypass mode H_BYP = 0. The relationship between CK_IN and FIR_CK in this and all
other modes is defined by Equation 1.
F_CLA
Bit FC0 is used to select the clear accumulator mode in the FIR. This mode is enabled
by setting F_CLA = 1 and is disabled by setting F_CLA = 0. In normal operation this bit
should be set equal to zero. This mode zeros the feedback path in the accumulator of
the multiplier/accumulator (MAC). It also allows the multiplier output to be clocked off
the chip by FIR_CK, thus DATA_RDY has no meaning in this mode. This mode can
be used in conjunction with the F_OAD bit to read out the FIR coefficients from the
coefficient RAM.
F_DIS
Bit FD0 is used to select the FIR disable mode. This feature enables the FIR
parameters to be changed. This feature is selected by setting F_DIS = 1. This mode
terminates the current FIR cycle. While this feature is selected, the HDF continues to
process data and write it into the FIR data RAM. When the FIR re-programming is
completed, the FIR can be re-enabled either by clearing F_DIS, or by asserting one of
the start inputs, which automatically clears F_DIS.
FIGURE 6.
7
HSP43220
DDF Control Regis ters (Continued)
H_Register 2 (A1 = 1, A0 = 1)
RESERVED
H_GROWTH
G5 G4 G3 G2 G1 G0
H_STAGES
N2
1
N1
0
N0
15 14 13 12 11 10
9
8
7
6
5
4
3
2
H_STAGES
Bits N0-N2 are used to select the number of stages or order of the
HDF filter. The number that is programmed in is equal to the
required number of stages. For a 5th order filter, H_STAGES
would be set equal to 5.
H_GROWTH
Bits G0-G5 are used to select the proper amount of growth bits.
H_GROWTH is calculated using the following equation:
H_GROWTH = 50 - CEILING {H_STAGES X log (H
DEC
)/ log(2)}
where the CEILING { } means use the next largest integer of the
result of the value in brackets and log is the log to the base 10.
The value of H_GROWTH represents the position of the LSB on
the output of the data shifter.
FIGURE 7.
Start Logic
The Start Logic generates a start signal that is used
internally to synchronously start the DDF. If ASTARTIN is
asserted (STARTIN must be tied high) the Start Logic
In using ASTARTIN or STARTIN a high to low transition
must be detected by the rising edge of CK_IN, therefore
these signals must have been high for more than one CK_IN
cycle and then taken low.
synchronizes it to CK_IN by double latching the signal and
generating the signal STARTOUT, which is shown in Figure
8. The STARTOUT signal is then used to synchronously
start other DDFs in a multi-chip configuration (the
STARTOUT signal of the first DDF would be tied to the
STARTIN of the second DDF). The NAND gate shown in
Figure 8 then passes this synchronized signal to be used on
chip to provide a synchronous start. Once started, the chip
requires a RESET to halt operation.
The FIR Section
The second filter in the top level block diagram is a Finite
Impulse Response (FIR) filter which performs the final
shaping of the signal spectrum and suppresses the aliasing
components in the transition band of the HDF. This enables
the DDF to implement filters with narrow pass bands and
sharp transition bands.
The FIR is implemented in a transversal structure using a single
multiplier/accumulator (MAC) and RAM for storage of the data
and filter coefficients as shown in Figure 9. The FIR can
implement up to 512 symmetric taps and decimation up to 16.
RESET
STARTIN
S
S
ASTARTIN
CK_IN
ISTART
D
Q
D
Q
The FIR is divided into 2 sections: the FIR filter section and
the FIR control logic.
STARTOUT
FIGURE 8. START LOGIC
Coefficient RAM
The Coefficient RAM stores the coefficients for the current FIR
filter being implemented. The coefficients are loaded into the
Coefficient RAM over the control bus (C_BUS). The
coefficients are written into the Coefficient RAM sequentially,
starting at location zero. It is only necessary to write one half
of the coefficients when symmetric filters are being
implemented, where the last coefficient to be written in is the
center tap.
When STARTIN is asserted (ASTARTIN must be tied high)
the NAND gate passes STARTIN which is used to provide the
internal start, ISTART, for the DDF. When RESET is asserted
the internal start signal is held inactive, thus it is necessary to
assert either ASTARTIN or STARTIN in order to start the
DDF. The timing of the first valid DATA_IN with respect to
START_IN is shown in the Timing Waveforms.
8
HSP43220
The coefficients are loaded into address 01 in two writes.
The first write loads the upper 16 bits of the 20-bit
section of the OPERATIONAL SECTION there is a chart that
shows the tradeoffs between these parameters.)
CK_IN[(TAPS/2) + 4 + F
]
coefficient, C4 through C19. The second write loads the
lower 4 bits of the coefficient, C0 through C3, where C19 is
the MSB. The two 16-bit writes are then formatted into the
20-bit coefficient that is then loaded into the Coefficient RAM
starting at RAM address location zero, where the coefficient
at this location is the outer tap (or the first coefficient value).
DEC
---------------------------------------------------------------------------------
FIR_CK ≥
(EQ. 1)
H
F
DEC DEC
This equation expresses the minimum FIR_CK. The
minimum FIR_CK is the smallest integer multiple of CK_IN
that satisfies Equation 1. In addition, the TSK specification
must be met (see AC Electrical Specifications). F
is the
DEC
= F_DRATE +1), where
To reload coefficients, the Coefficient RAM Address pointer
must be reset to location zero so that the coefficients will be
loaded in the order the FIR filter expects. There are two
methods that can be used to reset the Coefficient RAM
address pointer. The first is to assert RESET, which
decimation rate in the FIR (F
DEC
TAPS = the number of taps in the FIR for even length filters
and equals the number of taps+1 for odd length filters.
Solving the above equation for the maximum number of taps:
automatically resets the pointer, but also clears the HDF and
alters some of the control register bits. (RESET does not
change any of the coefficient values.) The second method is
to set the F_DIS bit in control register H_ REGISTER1. This
control bit allows any of the FIR control register bits to be re-
programmed, but does not automatically modify any control
registers. When the programming is completed, the FIR is
re-started by clearing the F_DIS bit or by asserting one of
the start inputs (ASTARTIN or STARTIN). The F_DIS bit
allows the filter parameters to be changed more quickly and
is thus the recommended reprogramming method.
FIR_CK H
F
DEC DEC
TAPS = 2 --------------------------------------------------------- – F
-4
(EQ. 2)
DEC
CK_IN
In using this equation, it must be kept in mind that CK_IN/
must be less than or equal to 4MHz (unless the HDF
H
DEC
is in bypass mode in which case this limitation in the HDF
does not apply). In the OPERATIONAL SECTION under the
Design Considerations, there is a table that shows the trade-
offs of these parameters. In addition, Intersil provides a
software package called DECIMATE™ which designs the
DDF filter from System specifications.
The registered outputs of the data RAM are added or
subtracted in the 17-bit pre-adder. The F_OAD control bit
allows zeros to be input into one side of the pre-adder. This
provides the capability to implement non-symmetric filters.
Data RAM
The Data RAM stores the data needed for the filter
calculation. The format of the data is:
0
-1 -2 -3 -4 -5 -6 -7 -8 -9 -10 -11 -12 -13 -14 -15
2 .2 2 2 2 2 2 2 2 2 2
0
2
2
2
2
2
The selection of adding the register outputs for an even
symmetric filter or for subtracting the register outputs for odd
symmetric filter is provided by the control bit F_ESYM, which
is programmed over the control bus. When subtraction is
selected, the new data is subtracted from the old data. The
17-bit output of the adder forms one input of the
multiplier/accumulator.
where the sign bit is in the 2 location.
The 16-bit output of the HDF Output Register is written into
the Data Ram on the rising edge of CK_DEC.
RESET initializes the write pointer to the data RAM. After a
RESET occurs, the output of the FIR will not be valid until
the number of new data samples written to the Data RAM
equals TAPS.
A control bit F_CLA provides the capability to clear the
feedback path in the accumulator such that multiplier output
will not be accumulated, but will instead flow directly to the
output register. The bit weightings of the data and
coefficients as they are processed in the FIR is shown
below.
The filter always operates on the most current sample and
the taps-1 previous samples. Thus if the F_DIS bit is set,
data continues to be written into the data RAM coming from
the HDF section. When the FIR is enabled again the filter will
be operating on the most current data samples and thus
another transient response will not occur.
0
-1
-15
Input Data (from HDF) 2 .2 . . . 2
1 0 -1 -15
Pre-adder Output 2 2 .2 . . . 2
The maximum throughput of the FIR filter is limited by the
use of a single Multiplier/Accumulator (MAC). The data
output from the HDF being clocked into the FIR filter by
CK_DEC must not be at a rate that causes an erroneous
result being calculated because data is being overwritten.
0
-1
-19
Coefficient 2 .2 . . . 2
8
0
1
-34
Accumulator 2 . . . 2 .2 . . . 2
FIR Output
The 40 most significant bits of the accumulator are latched
into the output register. The lower 3 bits are not brought to
the output. The 40 bits out of the output register are selected
to be output by a pair of multiplexers. This register is clocked
by FIR_CK (see Figure 9).
The equation shown below describes the relationship
between, FIR_CK, CK_DEC, the number of taps that can be
implemented in the FIR, the decimation rate in the HDF and
the decimation rate in the FIR. (In the Design Considerations
9
HSP43220
There are two multiplexers that route 24 of the 40 output bits
output bus, DATA_OUT0-15. The output formatter is shown
in detail in Figure 10.
from the output register to the output pins. The first
multiplexer selects the output register bits that will be routed
to output pins DATA_OUT16-23 and the second multiplexer
selects the output register bits that will be routed to output
pins DATA_OUT0-15.
FIR Control Logic
The DATA_RDY strobe indicates that new data is available on
the output of the FIR. The rising edge of DATA_RDY can be
used to load the output data into an external register or RAM.
The multiplexers are controlled by the control signal F_BYP
and the OUT_SELH pin. F_BYP and OUT_SELH both
control the first multiplexer that selects the upper 8 bits of
the output bus, DATA_OUT16-23. F_BYP controls the
second multiplexer that selects the lower 16 bits of the
Data Format
The DDF maintains 16 bits of accuracy in both the HDF and
FIR filter stages. The data formats and bit weightings are
shown in Figure 11.
PRE-ADDER LOGIC
REG
16
16
16
16 x 512
FROM HDF
DATA
REG
PRE-ADDER
F_ESYM
F_OAD
16
17
RAM
REG
16
20 x 256
FROM COEFFICIENT
COEFFICIENT
REG
20
REG
17
FORMATTER
20
20
17
RAM
17 x 20 BIT MULTIPLIER ARRAY
37
MULTIPLIER/
ACCUMULATOR
SECTION
FROM CONTROL REGISTERS
F_TAPS F_BYP
REG
37
F_DRATE
F_DIS
43
F_CLA
43-BIT ACCUMULATOR
43
FIR CONTROL LOGIC
FIR_CK
FIR_CK
OUTPUT REG
40
MUX
REG
DATA_RDY
F_CLA
OUTPUT
FORMATTER
24
DATA_RDY
DATA_OUT 0 -23
FIGURE 9. FIR FILTER
40
F_BYP = 0
OUT_SELH = 1
-16
-31
0
-15
8
8
16 16
MUX
2
- 2
2
- 2
8
1
-16
-23
F_BYP = 0
F_BYP = 1
2
- 2
2
- 2
F_BYP
F_BYP = 0
MUX
F_BYP
OUT_SELH = 0
OR
OUT_SELH
F_BYP = 1
8
16
OUT_ENX
OUT_ENP
DATA_OUT16-23
DATA_OUT0 -15
FIGURE 10. FIR OUTPUT FORMATTER
10
HSP43220
INPUT DATA FORMAT
Fractional Two's Complement Input
15
14
-1
13
-2
2
12
-3
2
11
-4
2
10
-5
2
9
8
7
6
5
4
3
2
1
0
0
-6
-7
-8
-9
-10 -11 -12 -13 -14 -15
-2 . 2
2
2
2
2
2
2
2
2
2
2
FIR COEFFICIENT FORMAT
Fractional Two's Complement Input
19
18
-1
17
-2
16
-3
2
15
-4
14
13
-6
12
-7
2
11
-8
2
10
-9
2
9
8
7
6
5
4
3
2
1
0
0
-5
-10 -11 -12 -13 -14 -15
-16 -17 -18 -19
-2 . 2
2
2
2
2
2
2
2
2
2
2
2
2
2
2
OUTPUT DATA FORMAT
Fractional Two's Complement Output
FOR: OUT_SELH = 1, F_BYP = 0
23 22 21 20 19 18 17 16
15
14
-1
13
-2
2
12
-3
2
11
-4
2
10
-5
2
9
8
7
6
5
-10
4
-11
3
-12
2
-13
1
-14
0
-15
8
7
6
5
4
3
2
1
0
-6
-7
-8
-9
-2
2
2
2
2
2
2
2
2
. 2
2
2
2
2
2
2
2
2
2
2
FOR: OUT_SELH = 0, F_BYP = 0
15
14
-1
13
-2
2
12
-3
2
11
-4
2
10
-5
2
9
8
7
6
5
-10
4
-11
3
-12
2
-13
1
-14
0
-15
23 22 21 20 19 18 17 16
0
-6
-7
-8
-9
-16 -17 -18 -19 -20 -21 -22 -23
-2 . 2
2
2
2
2
2
2
2
2
2
2
2
2
2
2
2
2
2
2
FOR: OUT_SELH = X, F_BYP = 1
23 22 21 20 19 18 17 16
-16 -17 -18 -19 -20 -21 -22 -23
15
14
13
12
11
10
9
-22
8
-23
7
-24
6
-25
5
-26
4
-27
3
-28
2
-29
1
-30
0
-31
-16
-17
-18
-19
-20
-21
2
2
2
2
2
2
2
2
2
2
2
2
2
2
2
2
2
2
2
2
2
2
2
2
FIGURE 11.
Operational Section
Start Configurations
Multi-Chip Start Configurations
The scenario to put the DDF into operational mode is: reset
the DDF by asserting the RESET input, configure the DDF
over the control bus, and apply a start signal, either by
ASTARTIN or STARTIN. Until the DDF is put in operational
mode with a start pulse, the DDF ignores all data inputs.
Since there are two methods to start up the DDF, there are also
two configurations that can be used to start up multiple chips.
The first method is shown in Figure 12. The timing of the
STARTOUT circuitry starts the second DDF on the same
clock as the first. If more DDFs are also to be started
synchronously, STARTOUT is connected to their
STARTIN's.
To use the asynchronous start, an asynchronous active low
pulse is applied to the ASTARTIN input. ASTARTIN is
internally synchronized to the sample clock, CK_IN, and
generates STARTOUT. This signal is also used internally
when the asynchronous mode is selected. It puts the DDF in
operational mode and allows the DDF to begin accepting
data. When the ASTARTIN input is being used, the
STARTIN input must be tied high to ensure proper
operation.
The second method to start up DDFs in a multiple chip
configuration is to use the synchronous start scenario.
The STARTIN input is wired to all the chips in the chain, and is
asserted by a active low synchronous pulse that has been
externally synchronized to CK_IN. In this way all DDFs are
synchronously started. The ASTARTIN input on all the chips is
tied high to prevent false starts. The STARTOUT outputs are all
left unconnected. This configuration is illustrated in Figure 13.
To start the DDF synchronously, the STARTIN is asserted
with a active low pulse that has been externally
synchronized to CK_IN. Internally the DDF then uses this
start pulse to put the DDF in operate mode and start
accepting data inputs. When STARTIN is used to start the
DDF the ASTARTIN input must be tied high to prevent false
starts.
11
HSP43220
TO OTHER DDF'S
+5V
STARTIN
+5V
ASTARTIN
STARTIN
STARTOUT
NC
DDF
DDF
ASTARTIN
STARTOUT
CK_IN
FIR_CK
CK_IN
FIR_CK
FIGURE 12. ASYNCHRONOUS START UP
+5V
ASTARTIN
STARTIN
STARTOUT
NC
STARTIN
DDF
DDF
+5V
CK_IN
ASTARTIN
STARTOUT
CK_IN
FIR_CK
FIR_CK
FIGURE 13. SYNCHRONOUS START UP
is over-sampled in order to capture a wide frequency band
containing many narrow band signals. The NCOM is “tuned”
to the frequency of the signal of interest and performs a
complex down conversion to baseband of this signal, which
results in a complex signal centered at baseband. A pair of
DDFs then low pass filters the NCOM output, extracting the
signal of interest.
Chip Set Application
The HSP43220 is ideally suited for narrow band filtering in
Communications, Instrumentation and Signal Processing
applications. The HSP43220 provides a fully integrated
solution to high order decimation filtering.
The combination of the HSP43220 and the HSP45116
(which is a NCOM Numerically Controlled Oscillator/
Modulator) provides a complete solution to digital receivers.
The diagram in Figure 14 illustrates this concept.
Des ign Trade-Off Cons iderations
Equation 2 in the Functional Description section expresses
the relationship between the number of TAPS which can be
implemented in the FIR as a function of CK_IN, FIR_CK,
The HSP45116 down converts the signal of interest to
baseband, generating a real component and an imaginary
component. A HSP43220 then performs low pass filtering
and reduces the sampling rate of each of the signals.
H
, F . Table 1 provides a tradeoff of these
DEC DEC
parameters. For a given speed grade and the ratio of the
clocks, and assuming minimum decimation in the HDF, the
number of FIR taps that can be implemented is given in
Equation 2.
The system scenario for the use of the DDF involves a
narrow band signal that has been over-sampled. The signal
HSP45116
NCOM
HSP43220
DDF
COS (WT)
SAMPLED
INPUT
DATA
HSP43220
DDF
SIN (WT)
0
10MHz
0
20MHz
0
FIGURE 14. DIGITAL CHANNELIZER
12
HSP43220
TABLE 1. DESIGN TRADE OFF FOR MINIMUM H
DEC
TAPS
FIR_CK
CK_IN
SPEEDGRADE
(MHz)
MIN H
F
= 1
F
= 2
F
= 4
F
= 8
F
= 16
DEC
DEC
DEC
DEC
DEC
DEC
33
25.6
15
1
1
1
2
2
2
4
4
4
8
8
8
9
7
4
5
4
2
3
2
1
2
1
1
8
24
56
120
248
4
16
4
40
16
64
48
16
80
48
16
112
48
48
88
40
184
88
(Note)
33
10
28
20
4
136
104
40
280
216
88
25.6
15
6
(Note)
14
33
36
20
4
168
104
40
344
216
88
25.6
15
6
(Note)
22
33
52
20
20
232
104
104
472
216
216
25.6
15
6
6
NOTE: Filter not realizable.
DECIMATE
Intersil provides a development system which assists the
design engineer to utilizing this filter. The DECIMATE
software package provides the user with both filter design
and simulation environments for filter evaluation and design.
These tools are integrated within one standard DSP CAD
environment, The Athena Group's Monarch Professional
DSP Software package.
This software package runs on an IBM™ PC™, XT™, AT™,
PS/2™ computer or 100% compatible with the following
configuration:
640K RAM
5.25” or 3.5” Floppy drive
hard disk
The software package is designed specifically for the DDF. It
provides all the filter design software for this proprietary
architecture. It provides a user-friendly menu driven
interface to allow the user to input system level filter
requirements. It provides the frequency response curves
and a data flow simulation of the specified filter design
(Figure 15). It also creates all the information necessary to
program the DDF, including a PROM file for programming
the control registers.
math co-processor
MS/PC-DOS 2.0 or higher
CGA, MCGA, EGA, VGA and
Hercules graphics adapters
For more information, see the description of DECIMATE in
the Development Tools Section of this data book.
13
HSP43220
FIGURE 15. DECIMATE DESIGN MODULE SCREENS
14
HSP43220
Absolute Maximum Ratings T = 25°C
Thermal Information
A
Supply Voltage. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . +6.0V
Input, Output or I/O Voltage Applied . . . . .GND -0.5V to V +0.5V
ESD Classification . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . Class 1
Thermal Resistance (Typical, Note 1)
θ
(°C/W)
35
JA
CC
PLCC Package. . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Maximum Storage Temperature Range . . . . . . . . . .-65°C to 150°C
Maximum Junction Temperature
PLCC Package. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 150°C
Maximum Lead Temperature (Soldering 10s) . . . . . . . . . . . . . 300°C
(PLCC - Lead Tips Only)
Operating Conditions
Temperature Range. . . . . . . . . . . . . . . . . . . . . . . . . . . . 0°C to 70°C
Voltage Range . . . . . . . . . . . . . . . . . . . . . . . . . . . . +4.75V to +5.25V
Die Characteristics
Component Count . . . . . . . . . . . . . . . . . . . . . . . 193,000 Transistors
CAUTION: Stresses above those listed in “Absolute Maximum Ratings” may cause permanent damage to the device. This is a stress only rating and operation of the
device at these or any other conditions above those indicated in the operational sections of this specification is not implied.
NOTE:
1. θ is measured with the component mounted on an evaluation PC board in free air.
JA
DC Electrical Specifications
PARAMETER
Logical One Input Voltage
Logical Zero Input Voltage
High Level Clock Input
SYMBOL
TEST CONDITIONS
MIN
2.0
-
MAX
-
UNITS
V
V
V
V
V
V
= 5.25V
= 4.75V
= 5.25V
= 4.75V
IH
CC
CC
CC
CC
V
0.8
-
V
IL
V
3.0
-
V
IHC
Low Level Clock Input
V
0.8
-
V
ILC
OH
Output HIGH Voltage
V
I
I
= -400µA, V
= 4.75V
= 4.75V
CC
2.6
-
V
OH
OL
CC
Output LOW Voltage
V
= +2.0mA, V
0.4
10
10
500
120
V
OL
Input Leakage Current
I
V
V
V
= V
or GND, V
= 5.25V
-10
-10
-
µA
µA
µA
mA
I
IN
CC
CC
I/O Leakage Current
I
= V
or GND, V
= 5.25V
O
OUT
CC
CC
Standby Power Supply Current
Operating Power Supply Current
I
= V
or GND V
= 5.25V, Note 3
CCSB
CCOP
IN
CC
CC
or GND, V
I
f = 15MHz, V = V
IN
= 5.25V,
CC
-
CC
Notes 2 and 4
Capacitance T = 25°C, Note 3
A
PARAMETER
Input Capacitance
Output Capacitance
NOTES:
SYMBOL
TEST CONDITIONS
FREQ = 1MHz, V = Open, All measurements
MIN
MAX
12
UNITS
pF
C
-
-
IN
CC
are referenced to device ground
C
10
pF
O
2. Power supply current is proportional to operating frequency. Typical rating for I
is 8mA/MHz.
CCOP
3. Not tested, but characterized at initial design and at major process/design changes.
4. Output load per test load circuit with switch open and C = 40pF.
L
15
HSP43220
AC Electrical Specifications
V
= +4.75V to +5.25V, T = 0°C to 70°C
A
CC
-15
-25
-33
PARAMETER
Input Clock Frequency
FIR Clock Frequency
Input Clock Period
SYMBOL
NOTES
MIN
0
MAX
MIN
0
MAX
MIN
0
MAX
UNITS
MHz
MHz
ns
F
15
15
-
25.6
33
33
-
CK
FIR
CK
F
0
0
25.6
0
t
66
66
26
26
0
39
39
16
16
0
-
-
-
-
30
30
13
13
0
FIR Clock Period
t
-
-
ns
FIR
Clock Pulse Width Low
Clock Pulse Width High
t
-
-
ns
SPWL
t
-
-
ns
SPWH
Clock Skew Between FIR_CK
and CK_IN
t
t
-25
t
-15
t
-15
ns
SK
FIR
FIR
FIR
CK_IN Pulse Width Low
CK_IN Pulse Width High
CK_IN Setup to FIR_CK
CK_IN Hold from FIR_CK
RESET Pulse Width Low
Recovery Time on RESET
ASTARTIN Pulse Width Low
STARTOUT Delay from CK_IN
STARTIN Setup to CK_IN
Setup Time on DATA_IN
Hold Time on All inputs
Write Pulse Width Low
t
Notes 5, 8
Notes 5, 8
Notes 5, 8
Notes 5, 8
29
29
27
2
-
-
-
-
-
-
-
19
19
17
2
-
-
-
-
-
-
-
19
19
17
2
-
-
-
-
-
-
-
ns
ns
ns
ns
ns
ns
ns
ns
ns
ns
ns
ns
ns
ns
CH1L
t
CH1H
t
CIS
CIH
t
t
4t
8t
4t
8t
4t
8t
RSPW
CK
CK
CK
CK
CK
CK
t
RTRS
t
t
+10
t
+10
t
+10
CK
AST
CK
CK
t
-
35
-
20
-
18
STOD
t
25
20
0
-
-
-
-
-
-
15
15
0
-
-
-
-
-
-
10
14
0
-
-
-
-
-
-
STIC
t
SET
t
HOLD
t
26
26
26
15
20
20
12
18
20
WL
Write Pulse Width High
t
WH
Setup Time on Address Bus Before
the Rising Edge of Write
t
STADD
Setup Time on Chip Select Before the
Rising Edge of Write
t
t
26
26
-
-
20
20
-
-
20
20
-
-
ns
ns
STCS
STCB
Setup Time on Control Bus Before the
Rising Edge of Write
DATA_RDY Pulse Width Low
t
2t -20
FIR
-
2t -10
FIR
-
2t -10
FIR
-
ns
ns
DRPWL
DATA_OUT Delay Relative to
FIR_CK
t
-
-
-
50
-
-
-
35
-
-
-
28
FIRDV
DATA RDY Valid Delay Relative
to FIR_CK
t
35
25
25
20
20
20
ns
ns
FIRDR
DATA_OUT Delay Relative to
OUT_SELH
t
t
OUT
OEV
Output Enable to Data Out Valid
Note 6
Note 5
-
-
15
15
-
-
15
15
-
-
15
15
ns
ns
Output Disable to Data Out
Three-State
t
OEZ
Output Rise, Output Fall Times
t , t
from 0.8V to
2V, Note 5
-
8
-
8
-
6
ns
r
f
NOTES:
5. Controlled by design or process parameters and not directly tested. Characterized upon initial design and after major process and/or design
changes.
6. Transition is measured at ±200mV from steady state voltage with loading as specified in test load circuit with and C = 40pF.
L
7. AC Testing is performed as follows: Input levels (CLK Input) 4.0V and 0V, Input levels (all other Inputs) 0V and 3.0V, Timing reference levels
(CLK) = 2.0V, (Others) = 1.5V, Output load per test load circuit and C = 40pF.
L
8. Applies only when H_BYP = 1 or H_DRATE = 0.
16
HSP43220
AC Tes t Load Circuit
S
1
DUT
C
(NOTE)
L
±
I
1.5V
I
OL
OH
SWITCH S1 OPEN FOR I
AND I
CCOP
CCSB
EQUIVALENT CIRCUIT
NOTE: Test head capacitance.
Timing Waveforms
t
FIR
FIR_CK
t
t
SET
t
SPWH
SPWL
t
t
CHIL
CHIH
t
CLK_IN
t
HOLD
SK
DATA_IN
CLK_IN
t
CK
FIGURE 16A.
FIGURE 16B.
FIGURE 16. INPUT TIMING
t
AST
ASTARTIN
RESET
t
RSPW
t
RTRS
CK_IN
WR
t
WL
t
STOD
STARTOUT
t
WH
t
HOLD
AO-1
C_BUS
CS
t
SET
CK_IN
t
t
t
STADD
HOLD
STIC
t
STARTIN
HOLD
t
t
STCB
HOLD
t
STCS
DATA_IN
FIGURE 17A.
FIGURE 17B.
FIGURE 17. START TIMING
17
HSP43220
Timing Waveforms (Continued)
FIR_CK
t
FIRDR
t
DATA_RDY
DATA_OUT 16-23
UPPER 8 BITS
FIRDR
t
DRPWL
LOWER 8 BITS
t
FIRDV
OUT_SELH
DATA_OUT
t
OUT
PREVIOUS OUTPUT
CURRENT OUTPUT
FIGURE 18A.
FIGURE 18B.
OUT_ENP
OUT_ENX
t
t
OEV
OEZ
2.0V
DATA_OUT 0-d23
DATA_OUT
1.7V
1.3V
0.8V
VALID
t
t
f
r
FIGURE 18D.
FIGURE 18C.
FIGURE 18.
All Intersil U.S. products are manufactured, assembled and tested utilizing ISO9000 quality systems.
Intersil Corporation’s quality certifications can be viewed at www.intersil.com/design/quality
Intersil products are sold by description only. Intersil Corporation reserves the right to make changes in circuit design, software and/or specifications at any time without
notice. Accordingly, the reader is cautioned to verify that data sheets are current before placing orders. Information furnished by Intersil is believed to be accurate and
reliable. However, no responsibility is assumed by Intersil or its subsidiaries for its use; nor for any infringements of patents or other rights of third parties which may result
from its use. No license is granted by implication or otherwise under any patent or patent rights of Intersil or its subsidiaries.
For information regarding Intersil Corporation and its products, see www.intersil.com
18
相关型号：
©2020 ICPDF网 联系我们和版权申明