ISL98001CQZ-240 [INTERSIL]
Triple Video Digitizer with Digital PLL; 三路视频数字化仪,数字锁相环型号: | ISL98001CQZ-240 |
厂家: | Intersil |
描述: | Triple Video Digitizer with Digital PLL |
文件: | 总29页 (文件大小:467K) |
中文: | 中文翻译 | 下载: | 下载PDF数据表文档文件 |
ISL98001
Key Features
®
Data Sheet
October 25, 2005
FN6148.0
Triple Video Digitizer with Digital PLL
Features
The ISL98001 3-channel, 8-bit Analog Front End (AFE)
contains all the functions necessary to digitize analog YPbPr
video signals and RGB graphics signals from DVD players,
digital VCRs, video set-top boxes, and personal computers.
This product family’s conversion rates support HDTV
resolutions up to 1080p and PC monitor resolutions up to
UXGA and QXGA, while the front end's programmable input
bandwidth ensures sharp, clear images at all resolutions.
• 140MSPS, 170MSPS, 210MSPS, 240MSPS, and
275MSPS maximum conversion rates
• Glitchless Macrovision®-compliant sync separator
• Extremely fast recovery from VCR head switching
• Low PLL clock jitter (250ps p-p @ 170MSPS)
• 64 interpixel sampling positions
• 0.35V
to 1.4V
video input range
p-p
p-p
To maximize performance with the widest variety of video
sources, the ISL98001 features a fast-responding digital PLL
(DPLL), providing extremely low jitter with PC graphics signals
and quick recovery from VCR head switching with video
signals. Integrated HSYNC and SOG processing eliminate the
need for external slicers, sync separators, Schmitt triggers,
and filters.
• Programmable bandwidth (100MHz to 780MHz)
• 2 channel input multiplexer
• RGB 4:4:4 and YUV 4:2:2 output formats
• 5 embedded voltage regulators allow operation from
single 3.3V supply and enhance performance, isolation
Glitchless, automatic Macrovision®-compliance is obtained
by a digital Macrovision® detection function that detects and
automatically removes Macrovision® from the HSYNC
signal.
• Completely independent 8-bit gain/10-bit offset control
• Pb-free plus anneal available (RoHS compliant)
Applications
• Digital TVs
Ease-of-use is also emphasized with features such as the
elimination of PLL charge pump current/VCO range
programming and single-bit switching between RGB and
YPbPr signals. Automatic Black Level Compensation
(ABLC™) eliminates part-to-part offset variation, ensuring
perfect black level performance in every application.
• Projectors
• Multifunction monitors
• Digital KVM
• RGB graphics processing
The ISL98001 is fully backwards compatible (hardware and
software) with the X980xx family of AFEs.
Simplified Block Diagram
Offset
DAC
ABLC™
Voltage
Clamp
3
RGB/YPbPrIN1
8 or 16
x3
RGB/YUVOUT
8 bit ADC
PGA
3
+
RGB/YPbPrIN2
HSYNCOUT
VSYNCOUT
SOGIN1/2
Sync
HSOUT
HSYNCIN1/2
VSYNCIN1/2
Digital PLL
PIXELCLKOUT
Processing
AFE Configuration and Control
CAUTION: These devices are sensitive to electrostatic discharge; follow proper IC Handling Procedures.
1-888-INTERSIL or 1-888-468-3774 | Intersil (and design) is a registered trademark of Intersil Americas Inc.
Copyright Intersil Americas Inc. 2005. All Rights Reserved
1
All other trademarks mentioned are the property of their respective owners.
ISL98001
Ordering Information
MAXIMUM
TEMPERATURE
RANGE (°C)
PACKAGE
(Pb-free)
PART NUMBER (Note)
PART MARKING
PIXEL RATE (MHz)
PKG. DWG. #
MDP0055
MDP0055
MDP0055
MDP0055
MDP0055
ISL98001CQZ-140
ISL98001CQZ-170
ISL98001CQZ-210
ISL98001CQZ-240
ISL98001CQZ-275
ISL98001CQ-140 Z
ISL98001CQ-170 Z
ISL98001CQ-210 Z
ISL98001CQ-240 Z
ISL98001CQ-275 Z
140
170
210
240
275
0 to 70
0 to 70
0 to 70
0 to 70
0 to 70
128 MQFP
128 MQFP
128 MQFP
128 MQFP
128 MQFP
NOTE: Intersil Pb-free plus anneal products employ special Pb-free material sets; molding compounds/die attach materials and 100%
matte tin plate termination finish, which are RoHS compliant and compatible with both SnPb and Pb-free soldering operations. Intersil
Pb-free products are MSL classified at Pb-free peak reflow temperatures that meet or exceed the Pb-free requirements of IPC/JEDEC
J STD-020.
Block Diagram
VCLAMP
Offset
DAC
10
ABLC™
RIN1
RIN2
VIN+
VIN-
8
8
RP[7:0]
RS[7:0]
8
8
8
8 bit ADC
PGA
PGA
PGA
+
+
+
VCLAMP
Offset
DAC
10
ABLC™
GIN1
RGBGND1
VIN+
VIN-
8
8
GP[7:0]
GS[7:0]
8 bit ADC
GIN2
RGBGND2
VCLAMP
Offset
DAC
10
ABLC™
BIN1
BIN2
VIN+
VIN-
8
8
BP[7:0]
BS[7:0]
8 bit ADC
DATACLK
DATACLK
SOGIN1
SOGIN2
HSYNCIN1
Sync
AFE Configuration
and Control
HSOUT
VSOUT
HSYNCIN2
VSYNCIN1
Processing
VSYNCIN2
HSYNCOUT
VSYNCOUT
CLOCKINV
Digital PLL
XTALIN
XTALOUT
XCLKOUT
SCL
SDA
Serial
Interface
SADDR
FN6148.0
2
October 25, 2005
ISL98001
Absolute Maximum Ratings
Thermal Information
Thermal Resistance
MQFP Package . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Maximum Biased Junction Temperature . . . . . . . . . . . . . . . . . . 125°C
Storage Temperature . . . . . . . . . . . . . . . . . . . . . . . .-65°C to +150°C
Voltage on V , V , or V
θ
(°C/W)
30
A
D
X
JA
(referenced to GND = GND = GND ). . . . . . . . . . . . . . . . . 4.0V
A
D
X
Voltage on any Analog Input Pin
(referenced to GND ). . . . . . . . . . . . . . . . . . . . . . . . . . -0.3V to V
A
A
Voltage on any Digital Input Pin
(referenced to GND ). . . . . . . . . . . . . . . . . . . . . . . -0.3V to +6.0V
D
Recommended Operating Conditions
Current into any Output Pin . . . . . . . . . . . . . . . . . . . . . . . . . . ±20mA
ESD Classification
Temperature (Commercial) . . . . . . . . . . . . . . . . . . . . . 0°C to +70°C
Supply Voltage. . . . . . . . . . . . . . . . . . . . . . . . . V = V = V = 3.3V
Human Body Model . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 2000V
Machine Model . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 200V
A
D
X
CAUTION: Stresses above those listed in “Absolute Maximum Ratings” may cause permanent damage to the device. This is a stress only rating and operation of the
device at these or any other conditions above those indicated in the operational sections of this specification is not implied.
Electrical Specifications Specifications apply for V = V = V = 3.3V, pixel rate = 140MHz for ISL98001-140, 170MHz for
A
D
X
ISL98001-170, 210MHz for ISL98001-210, 240MHz for ISL98001-240, 275MHz for ISL98001-275,
f
= 25MHz, T = 25°C, unless otherwise noted
A
XTAL
SYMBOL
PARAMETER
COMMENT
MIN
TYP
MAX
UNIT
FULL CHANNEL CHARACTERISTICS
Conversion Rate
ISL98001-140
Per Channel
10
10
10
10
10
8
140
170
210
240
275
MHz
MHz
MHz
MHz
MHz
Bits
ISL98001-170
ISL98001-210
ISL98001-240
ISL98001-275
ADC Resolution
Missing Codes
Guaranteed monotonic
None
DNL
(Full-
Channel)
Differential Non-Linearity
ISL98001-140
±0.5
±0.5
±0.6
±0.6
±0.7
+1.0/-0.9
+1.0/-0.9
+1.0/-0.9
+1.1/-0.9
+1.2/-0.9
LSB
LSB
LSB
LSB
LSB
ISL98001-170
ISL98001-210
ISL98001-240
ISL98001-275
INL
(Full-
Channel)
Integral Non-Linearity
ISL98001-140
±1.1
±1.1
±1.25
±1.5
±1.6
±6
±2.75
±3.25
±3.25
±3.5
LSB
LSB
LSB
LSB
LSB
dB
ISL98001-170
ISL98001-210
ISL98001-240
ISL98001-275
±3.75
Gain Adjustment Range
Gain Adjustment Resolution
Gain Matching Between Channels
8
Bits
%
Percent of full scale
±1
Full Channel Offset Error,
ABLC™ enabled
ADC LSBs,
±0.125
±0.5
1.4
LSB
over time and temperature
Offset Adjustment Range
(ABLC™ enabled or disabled)
ADC LSBs (See ABLC™
applications information section)
±127
LSB
ANALOG VIDEO INPUT CHARACTERISTICS (R 1, G 1, B 1, R 2, G 2, B 2)
IN
IN
IN
IN
IN
IN
Input Range
0.35
0.7
V
P-P
FN6148.0
3
October 25, 2005
ISL98001
Electrical Specifications Specifications apply for V = V = V = 3.3V, pixel rate = 140MHz for ISL98001-140, 170MHz for
A
D
X
ISL98001-170, 210MHz for ISL98001-210, 240MHz for ISL98001-240, 275MHz for ISL98001-275,
f
= 25MHz, T = 25°C, unless otherwise noted (Continued)
A
XTAL
SYMBOL
PARAMETER
Input Bias Current
COMMENT
MIN
TYP
±0.01
5
MAX
UNIT
µA
DC restore clamp off
±1
Input Capacitance
pF
Full Power Bandwidth
Programmable
780
MHz
INPUT CHARACTERISTICS (SOG 1, SOG 2)
IN
IN
V
/V
Input Threshold Voltage
Programmable - see register
listing for details
0 to
-0.3
V
IH IL
Hysteresis
Centered around threshold
40
5
mV
pF
Input Capacitance
INPUT CHARACTERISTICS (HSYNC 1, HSYNC 2)
IN
IN
V
/V
Input Threshold Voltage
Programmable - see register
listing for details
0.4 to
3.2
V
IH IL
Hysteresis
Centered around threshold
voltage
240
mV
R
C
Input Impedance
Input Capacitance
1.2
5
kΩ
IN
pF
IN
DIGITAL INPUT CHARACTERISTICS (SDA, SADDR, CLOCKINV , RESET)
IN
V
Input HIGH Voltage
Input LOW Voltage
Input Leakage Current
Input Capacitance
2.0
1.45
2.4
V
V
IH
V
0.8
IL
I
RESET has a 70kΩ pullup to V
±10
5
nA
pF
D
SCHMITT DIGITAL INPUT CHARACTERISTICS (SCL, VSYNC 1, VSYNC 2)
IN
IN
V +
Low to High Threshold Voltage
High to Low Threshold Voltage
Input Leakage Current
V
V
T
V -
T
0.95
I
±10
5
nA
pF
Input Capacitance
DIGITAL OUTPUT CHARACTERISTICS (DATACLK, DATACLK)
Output HIGH Voltage, I = 16mA
V
V
V
OH
O
V
Output LOW Voltage, I = -16mA
0.4
0.4
OL
O
DIGITAL OUTPUT CHARACTERISTICS (R , G , B , R , G , B , HS
, VS
, HSYNC
, VSYNC
)
P
P
P
S
S
S
OUT
OUT
OUT
OUT
V
Output HIGH Voltage, I = 8mA
2.4
V
V
OH
O
V
Output LOW Voltage, I = -8mA
O
OL
R
Pulldown to GND when Three-state
R , G , B , R , G , B only
56
kΩ
TRI
D
P
P
P
S
S
S
DIGITAL OUTPUT CHARACTERISTICS (SDA, XCLK
)
OUT
V
Output HIGH Voltage, I = 4mA
XCLK only; SDA is open-drain
OUT
2.4
V
V
OH
O
V
Output LOW Voltage, I = -4mA
0.4
OL
O
POWER SUPPLY REQUIREMENTS
V
Analog Supply Voltage
3
3
3
3.3
3.3
3.3
3.6
3.6
3.6
200
V
V
A
V
V
Digital Supply Voltage
D
X
Crystal Oscillator Supply Voltage
Analog Supply Current
V
I
mA
A
FN6148.0
4
October 25, 2005
ISL98001
Electrical Specifications Specifications apply for V = V = V = 3.3V, pixel rate = 140MHz for ISL98001-140, 170MHz for
A
D
X
ISL98001-170, 210MHz for ISL98001-210, 240MHz for ISL98001-240, 275MHz for ISL98001-275,
f
= 25MHz, T = 25°C, unless otherwise noted (Continued)
A
XTAL
SYMBOL
PARAMETER
Digital Supply Current
COMMENT
MIN
TYP
MAX
200
2
UNIT
mA
I
With grayscale ramp input
D
I
Crystal Oscillator Supply Current
1.4
mA
X
P
Total Power Dissipation
ISL98001-140
D
With grayscale ramp input
With grayscale ramp input
With grayscale ramp input
With grayscale ramp input
With grayscale ramp input
ADCs, PLL powered down
0.95
1.05
1.10
1.15
1.20
50
1.10
1.15
1.20
1.25
1.30
80
W
W
ISL98001-170
ISL98001-210
ISL98001-240
ISL98001-275
Standby Mode
W
W
W
mW
AC TIMING CHARACTERISTICS
PLL Jitter
250
450
ps p-p
Sampling Phase Steps
Sampling Phase Tempco
5.6° per step
64
±1
±3
ps/°C
°
Sampling Phase
Differential Nonlinearity
Degrees out of 360°
HSYNC Frequency Range
10
23
23
150
27
kHz
MHz
MHz
f
Crystal Frequency Range
25
25
XTAL
f
Frequency Range with External 3.3V Clock
33.5
XTALIN
Signal Driving XTAL
IN
t
DATA Valid Before Rising Edge of
DATACLK
15pF DATACLK load, 15pF DATA
load (Note 1)
1.3
2.0
ns
ns
SETUP
t
DATA Valid After Rising Edge of DATACLK 15pF DATACLK load, 15pF DATA
load (Note 1)
HOLD
AC TIMING CHARACTERISTICS (2-WIRE INTERFACE)
f
SCL Clock Frequency
0
400
kHz
ns
SCL
Maximum Width of a Glitch on SCL that Will 2 XTAL periods min
be Suppressed
80
t
SCL LOW to SDA Data Out Valid
5 XTAL periods plus SDA’s RC
time constant
See
comment
µs
µs
AA
t
Time the Bus Must be Free Before a New
Transmission Can Start
1.3
BUF
t
Clock LOW Time
1.3
0.6
0.6
0.6
100
0
µs
µs
µs
µs
ns
ns
µs
ns
LOW
t
Clock HIGH Time
HIGH
t
Start Condition Setup Time
Start Condition Hold Time
Data In Setup Time
SU:STA
HD:STA
SU:DAT
HD:DAT
SU:STO
t
t
t
Data In Hold Time
t
Stop Condition Setup Time
Data Output Hold Time
0.6
160
t
4 XTAL periods min
DH
NOTE:
1. Setup and hold times are specified for a 170MHz DATACLK rate.
FN6148.0
5
October 25, 2005
ISL98001
t
t
t
t
R
F
HIGH
LOW
SCL
SDA IN
t
SU:DAT
t
t
t
SU:STO
SU:STA
HD:DAT
t
HD:STA
t
t
t
BUF
AA
DH
SDA OUT
FIGURE 1. 2-WIRE INTERFACE TIMING
DATACLK
DATACLK
Pixel Data
tHOLD
tSETUP
FIGURE 2. DATA OUTPUT SETUP AND HOLD TIMING
The HSYNC edge (programmable leading or trailing) that the DPLL is locked to.
HSYNCIN
The sampling phase setting determines its relative position to the rest of the AFE’s output signals
tHSYNCin-to-HSout = 7.5ns + (PHASE/64 +8.5)*tPIXEL
Analog
P0
P1
P2
P3
P4
P5
P6
P7
P8
P9
P10
P11
P12
Video In
DATACLK
RP/GP/BP[7:0]
RS/GS/BS[7:0]
HSOUT
8 DATACLK Pipeline Latency
D0
D1
D2
D3
Programmable
Width and Polarity
FIGURE 3. 24-BIT OUTPUT MODE
FN6148.0
October 25, 2005
6
ISL98001
The HSYNC edge (programmable leading or trailing) that the DPLL is locked to.
The sampling phase setting determines its relative position to the rest of the AFE’s output signals
HSYNCIN
tHSYNCin-to-HSout = 7.5ns + (PHASE/64 +8.5)*tPIXEL
Analog
P0
P1
P2
P3
P4
P5
P6
P7
P8
P9
P10
P11
P12
Video In
DATACLK
GP[7:0]
RP[7:0]
BP[7:0]
HSOUT
8.5 DATACLK Pipeline Latency
G0 (Yo) G1 (Y1) G2 (Y2)
B0 (Uo) R1 (V1) B2 (U2)
Programmable
Width and Polarity
FIGURE 4. 24-BIT 4:2:2 OUTPUT MODE (FOR YUV SIGNALS)
The HSYNC edge (programmable leading or trailing) that the DPLL is locked to.
HSYNCIN
The sampling phase setting determines its relative position to the rest of the AFE’s output signals
tHSYNCin-to-HSout = 7.5ns + (PHASE/64 +10.5)*tPIXEL
Analog
Video In
P0
P1
P2
P3
P4
P5
P6
P7
P8
P9
P10
P11
P12
DATACLK
RP/GP/BP[7:0]
RS/GS/BS[7:0]
HSOUT
D0
D2
D3
D1
Programmable
Width and Polarity
FIGURE 5. 48-BIT OUTPUT MODE
FN6148.0
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October 25, 2005
ISL98001
The HSYNC edge (programmable leading or trailing) that the DPLL is locked to.
HSYNCIN
The sampling phase setting determines its relative position to the rest of the AFE’s output signals
tHSYNCin-to-HSout = 7.5ns + (PHASE/64 +8.5)*tPIXEL
Analog
Video In
P1
P2
P3
P4
P5
P6
P7
P8
P9
P10
P11
P0
DATACLK
RP/GP/BP[7:0]
RS/GS/BS[7:0]
HSOUT
D0
D2
D1
Programmable
Width and Polarity
FIGURE 6. 48-BIT OUTPUT MODE, INTERLEAVED TIMING
FN6148.0
October 25, 2005
8
ISL98001
Pin Configuration (MQFP, ISL98001CQZ-xxx)
NC
NC
1
2
3
4
5
6
7
8
9
102 RS5
101 RS6
100 RS7
99 VD
GNDA
VBYPASS
GNDA
VA
GNDD
98
97 GP0
96 GP1
RIN1
GP2
GNDA
95
VBYPASS
94 GP3
93 GP4
92 GP5
91 GP6
90 GP7
89 VD
GNDA 10
VA 11
GIN
RGBGND
SOGIN
1
1
1
12
13
14
GNDA 15
VBYPASS 16
GNDA 17
VA 18
88 GNDD
GS0
87
86 GS1
85 GS2
GS3
BIN1
19
84
VA 20
83 GS4
82 GS5
81 GS6
80 GS7
79 VCORE
78 GNDD
77 VD
GNDA 21
RIN2
22
GNDA 23
GIN
RGBGND
SOGIN
2
2
2
24
25
26
GNDD
GNDA 27
BIN 28
76
2
75 BP0
74 BP1
VA 29
GNDA 30
BP2
73
VCOREADC 31
GNDD 32
72 BP3
71 BP4
70 BP5
69 BP6
HSYNCIN
1
33
HSYNCIN2 34
VA 35
BP7
68
GNDA 36
GNDX 37
VX 38
67 VD
66 GNDD
VREGIN
65
FN6148.0
October 25, 2005
9
ISL98001
Pin Descriptions
SYMBOL
MQFP PIN #(s)
DESCRIPTION
R
G
1
1
7
Analog input. Red channel 1. DC couple or AC couple through 0.047µF.
Analog input. Green channel 1. DC couple or AC couple through 0.047µF.
Analog input. Blue channel 1. DC couple or AC couple through 0.047µF.
IN
12
19
13
IN
B
1
IN
RGB
1
Analog input. Ground reference for the R, G, and B inputs of channel 1 in the DC coupled configuration.
Connect to the same ground as channel 1's R, G, and B termination resistors. This signal is not used in the
GND
AC-coupled configuration, but the pin should still be tied to GND .
A
SOG
1
14
33
Analog input. Sync on Green. Connect to G 1 through a 0.01µF capacitor in series with a 500Ω resistor.
IN
IN
HSYNC
1
1
Digital input, 5V tolerant, 240mV hysteresis, 1.2kΩ impedance to GND . Connect to channel 1's HSYNC
IN
A
signal through a 680Ω series resistor.
VSYNC
44
22
24
28
25
Digital input, 5V tolerant, 500mV hysteresis. Connect to channel 1's VSYNC signal.
Analog input. Red channel 2. DC couple or AC couple through 0.047µF.
Analog input. Green channel 2. DC couple or AC couple through 0.047µF.
Analog input. Blue channel 2. DC couple or AC couple through 0.047µF.
IN
R
G
2
IN
2
IN
B
2
IN
RGB
2
Analog input. Ground reference for the R, G, and B inputs of channel 2 in the DC coupled configuration.
Connect to the same ground as channel 1's R, G, and B termination resistors. This signal is not used in the
GND
AC-coupled configuration, but the pin should still be tied to GND .
A
SOG
2
26
34
Analog input. Sync on Green. Connect to G 1 through a 0.01µF capacitor in series with a 500Ω resistor.
IN
IN
HSYNC
2
2
Digital input, 5V tolerant, 240mV hysteresis, 1.2kΩ impedance to GND . Connect to channel 2's HSYNC
IN
A
signal through a 680Ω series resistor.
VSYNC
45
41
Digital input, 5V tolerant, 500mV hysteresis. Connect to channel 2's VSYNC signal.
Digital input, 5V tolerant. When high, changes the pixel sampling phase by 180 degrees. Toggle at frame rate
IN
CLOCKINV
IN
during VSYNC to allow 2x undersampling to sample odd and even pixels on sequential frames. Tie to D
if unused.
GND
RESET
46
39
40
47
Digital input, 5V tolerant, active low, 70kΩ pullup to V . Take low for at least 1µs and then high again to reset
D
the ISL98001. This pin is not necessary for normal use and may be tied directly to the V supply.
D
XTAL
Analog input. Connect to external 24.5MHz to 27MHz crystal and load capacitor (See crystal spec for
IN
recommended loading). Typical oscillation amplitude is 1.0V
centered around 0.5V.
P-P
XTAL
XCLK
Analog output. Connect to external 24.5MHz to 27MHz crystal and load capacitor (See crystal spec for
OUT
recommended loading). Typical oscillation amplitude is 1.0V
centered around 0.5V.
P-P
3.3V digital output. Buffered crystal clock output at f
system components.
or f
/2. May be used as system clock for other
XTAL
OUT
XTAL
SADDR
SCL
48
50
Digital input, 5V tolerant. Address = 0x4C when tied low. Address = 0x4D when tied high.
Digital input, 5V tolerant, 500mV hysteresis. Serial data clock for 2-wire interface.
Bidirectional Digital I/O, open drain, 5V tolerant. Serial data I/O for 2-wire interface.
3.3V digital output. Red channel, primary pixel data. 56K pulldown when three-stated.
3.3V digital output. Red channel, secondary pixel data. 56K pulldown when three-stated.
3.3V digital output. Green channel, primary pixel data. 56K pulldown when three-stated.
3.3V digital output. Green channel, secondary pixel data. 56K pulldown when three-stated.
3.3V digital output. Blue channel, primary pixel data. 56K pulldown when three-stated.
3.3V digital output. Blue channel, secondary pixel data. 56K pulldown when three-stated.
SDA
49
R [7:0]
112-119
100-107
90-97
80-87
68-75
55-62
121
P
R [7:0]
S
G [7:0]
P
G [7:0]
S
B [7:0]
P
B [7:0]
S
DATACLK
3.3V digital output. Data clock output. Equal to pixel clock rate in 24-bit mode, one half of pixel clock rate in
48-bit mode.
DATACLK
122
125
3.3V digital output. Inverse of DATACLK.
HS
3.3V digital output. HSYNC output aligned with pixel data. Use this output to frame the digital output data.
This output is always purely horizontal sync (without any composite sync signals).
OUT
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October 25, 2005
ISL98001
Pin Descriptions (Continued)
SYMBOL
MQFP PIN #(s)
DESCRIPTION
VS
126
3.3V digital output. Artificial VSYNC output aligned with pixel data. VS
is generated 8 pixel clocks after
OUT
OUT
the trailing edge of HS
. This signal is usually not needed.
OUT
HSYNC
127
128
3.3V digital output. Buffered HSYNC (or SOG or CSYNC) output. This is typically used for measuring HSYNC
period. This output will pass composite sync signals and Macrovision signals if present on HSYNC or
OUT
OUT
IN
SOG
.
IN
VSYNC
3.3V digital output. Buffered VSYNC output. For composite sync signals, this output will be asserted for the
duration of the disruption of the normal HSYNC pattern. This is typically used for measuring VSYNC period.
V
6, 11, 18, 20, 29, Power supply for the analog section. Connect to a 3.3V supply and bypass each pin to GND with 0.1µF.
A
A
35
GND
3, 5, 8, 10, 15, Ground return for V and V
A
.
BYPASS
A
D
X
17, 21, 23, 27,
30, 36
V
54, 67, 77, 89, Power supply for all digital I/Os. Connect to a 3.3V supply and bypass each pin to GND with 0.1µF.
D
99, 111, 124
D
GND
32, 43, 51, 53, Ground return for V , V
D
, V
, and V
.
PLL
CORE COREADC
66, 76, 78, 88,
98, 108, 110,
120, 123
V
38
37
Power supply for crystal oscillator. Connect to a 3.3V supply and bypass to GND with 0.1µF.
X
X
GND
Ground return for V .
X
V
4, 9, 16
65
Bypass these pins to GND with 0.1µF. Do not connect these pins to each other or anything else.
A
BYPASS
VREG
3.3V input voltage for V
voltage regulator. Connect to a 3.3V source and bypass to GND with 0.1µF.
CORE D
IN
VREG
64
Regulated output voltage for V
, V
and V
; typically 1.9V. Connect only to V , V
PLL COREADC
OUT
PLL COREADC
CORE
and V
and bypass at input pins as instructed below. Do not connect to anything else - this output can
CORE
only supply power to V
, V
and V
.
PLL COREADC
CORE
V
31
42
Internal power for the ADC’s digital logic. Connect to VREG
with 0.1µF.
through a 10Ω resistor and bypass to GND
through a 10Ω resistor and bypass to GND
COREADC
OUT
OUT
D
D
V
Internal power for the PLL’s digital logic. Connect to VREG
with 0.1µF.
PLL
V
52, 79, 109
1, 2, 63
Internal power for core logic. Connect to VREG
and bypass each pin to GND with 0.1µF.
OUT D
CORE
NC
Reserved. Do not connect anything to these pins.
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ISL98001
Register Listing
ADDRESS
REGISTER (DEFAULT VALUE)
BIT(S) FUNCTION NAME
DESCRIPTION
1 = initial silicon, 2 = second revision, etc.
1 = ISL98001
0x00
Device ID
(read only)
3:0
7:4
0
Device Revision
Device ID
0x01
SYNC Status
(read only)
HSYNC1 Active
0: HSYNC1 is Inactive
1: HSYNC1 is Active
1
2
3
4
5
6
7
0
1
2
3
4
5
HSYNC2 Active
VSYNC1 Active
VSYNC2 Active
SOG1 Active
SOG2 Active
PLL Locked
0: HSYNC2 is Inactive
1: HSYNC2 is Active
0: VSYNC1 is Inactive
1: VSYNC1 is Active
0: VSYNC2 is Inactive
1: VSYNC2 is Active
0: SOG1 is Inactive
1: SOG1 is Active
0: SOG2 is Inactive
1: SOG2 is Active
0: PLL is unlocked
1: PLL is locked to incoming HSYNC
CSYNC Detect at
Sync Splitter
0: Composite Sync signal not detected
1: Composite Sync signal is detected
0x02
SYNC Polarity
(read only)
HSYNC1
Polarity
0: HSYNC1 is Active High
1: HSYNC1 is Active Low
HSYNC2
Polarity
0: HSYNC2 is Active High
1: HSYNC2 is Active Low
VSYNC1
Polarity
0: VSYNC1 is Active High
1: VSYNC1 is Active Low
VSYNC2
Polarity
0: VSYNC2 is Active High
1: VSYNC2 is Active Low
HSYNC1
Trilevel
0: HSYNC1 is Standard Sync
1: HSYNC1 is Trilevel Sync
HSYNC2
Trilevel
0: HSYNC2 is Standard Sync
1: HSYNC2 is Trilevel Sync
7:6
2:0
N/A
Returns 0
0x03
0x04
HSYNC Slicer (0x33)
HSYNC1 Threshold 000 = lowest (0.4V) All values referred to
011 = default (1.6V) voltage at HSYNC input
111 = highest (3.2V) pin, 240mV hysteresis
3
6:4
7
Reserved
Set to 00
HSYNC2 Threshold See HSYNC1
Disable Glitch Filter 0: HSYNC/VSYNC Glitch Filter Enabled (default)
1: HSYNC/VSYNC Glitch Filter Disabled
SOG Slicer (0x16)
3:0
4
SOG1 and SOG2
Threshold
0x0 = lowest (0mV)
0x6 = default (120mV) 20mV step size
0xF = highest (300mV)
SOG Filter
Enable
0: SOG low pass filter disabled
1: SOG low pass filter enabled, 14MHz corner
(default)
5
SOG Hysteresis
Disable
0: 40mV SOG hysteresis enabled
1: 40mV SOG hysteresis disabled (default)
7:6
Reserved
Set to 00.
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12
ISL98001
Register Listing (Continued)
ADDRESS
REGISTER (DEFAULT VALUE)
BIT(S) FUNCTION NAME
DESCRIPTION
0x05
Input configuration (0x00)
0
Channel Select
0: VGA1
1: VGA2
1
Input Coupling
0: AC coupled (positive input connected to clamp
DAC during clamp time, negative input disconnected
from outside pad and always internally tied to
appropriate clamp DAC).
1: DC coupled (+ and - inputs are brought to pads and
never connected to clamp DACs). Analog clamp
signal is turned off in this mode.
2
RGB/YPbPr
Sync Type
0: RGB inputs
Base ABLC target code = 0x00 for R, G, and B)
1: YPbPr inputs
Base ABLC target code = 0x00 for G (Y)
Base ABLC target code = 0x80 for R (Pr) and B (Pb)
3
4
0: Separate HSYNC/VSYNC
1: Composite (from SOG or CSYNC on HSYNC)
Composite Sync
Source
0: SOG
IN
1: HSYNC
IN
Note: If Sync Type = 0, the multiplexer will pass
HSYNC regardless of the state of this bit.
IN
5
6
COAST CLAMP
enable
0: DC restore clamping and ABLC™ suspended
during COAST.
1: DC restore clamping and ABLC™ continue during
COAST.
Sync Mask Disable 0: Interval between HSYNC pulses masked
(preventing PLL from seeing Macrovision and any
spurious glitches).
1: Interval between HSYNC pulses not masked
(Macrovision will cause PLL to lose lock).
7
HSYNC
Disable
Mask
0: HSYNC
signal is masked (any Macrovision,
OUT
OUT
sync glitches on incoming SYNC are stripped from
HSYNC
).
OUT
OUT
1: HSYNC
signal is not masked (any
Macrovision, sync glitches on incoming SYNC
appear on HSYNC
).
OUT
If Sync Mask Disable = 1, HSYNC
is not masked.
OUT
0x06
0x07
7:0
7:0
Red Gain
Channel gain, where:
Red Gain (0x55)
gain (V/V) = 0.5 + [7:0]/170
0x00: gain = 0.5V/V
(1.4V
input = full range of ADC)
P-P
Green Gain
0x55: gain = 1.0V/V
(0.7V input = full range of ADC)
Green Gain (0x55)
Blue Gain (0x55)
P-P
0xFF: gain = 2.0V/V
(0.35V input = full range of ADC)
0x08
7:0
Blue Gain
P-P
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ISL98001
Register Listing (Continued)
ADDRESS
REGISTER (DEFAULT VALUE)
BIT(S) FUNCTION NAME
DESCRIPTION
0x09
7:0
7:0
7:0
0
Red Offset
Green Offset
Blue Offset
ABLC™ enabled: digital offset control. A 1LSB change
in this register will shift the ADC output by 1 LSB.
ABLC™ disabled: analog offset control. These bits go
to the upper 8-bits of the 10-bit offset DAC. A 1LSB
change in this register will shift the ADC output
approximately 1 LSB (Offset DAC range = 0) or
0.5LSBs (Offset DAC range = 1).
Red Offset (0x80)
0x0A
0x0B
0x0C
Green Offset (0x80)
0x00 = min DAC value or -0x80 digital offset,
0x80 = mid DAC value or 0x00 digital offset,
0xFF = max DAC value or +0x7F digital offset
Blue Offset (0x80)
Offset DAC Configuration (0x00)
Offset DAC Range
Reserved
0: ±½ ADC fullscale (1 DAC LSB ~ 1 ADC LSB)
1: ±¼ ADC fullscale (1 DAC LSB ~ ½ ADC LSB)
1
Set to 0.
3:2
Red Offset DAC
LSBs
These bits are the LSBs necessary for 10-bit manual
offset DAC control.
Combine with their respective MSBs in registers
0x09, 0x0A, and 0x0B to achieve 10-bit offset DAC
control.
5:4
7:6
Green Offset DAC
LSBs
Blue Offset DAC
LSBs
0x0D
AFE Bandwidth (0x2E)
0
Unused
Value doesn’t matter
3:1
AFE BW
3dB point for AFE lowpass filter
000b: 100MHz
111b: 780MHz (default)
7:4
Peaking
0x0: Peaking off
0x1: Moderate peaking
0x2: Maximum recommended peaking (default)
Values above 2 are not recommended.
0x0E
0x0F
PLL Htotal MSB (0x03)
PLL Htotal LSB (0x20)
5:0
7:0
PLL Htotal MSB
PLL Htotal LSB
14-bit HTOTAL (number of active pixels) value
The minimum HTOTAL value supported is 0x200.
HTOTAL to PLL is updated on LSB write only.
0x10
PLL Sampling Phase (0x00)
5:0
PLL Sampling Phase Used to control the phase of the ADC’s sample point
relative to the period of a pixel. Adjust to obtain
optimum image quality. One step = 5.625° (1.56% of
pixel period).
0x11
0x12
PLL Pre-coast (0x04)
PLL Post-coast (0x04)
7:0
7:0
Pre-coast
Number of lines the PLL will coast prior to the start of
VSYNC.
Post-coast
Number of lines the PLL will coast after the end of
VSYNC.
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ISL98001
Register Listing (Continued)
ADDRESS
REGISTER (DEFAULT VALUE)
BIT(S) FUNCTION NAME
DESCRIPTION
0x13
PLL Misc (0x04)
0
PLL Lock Edge
HSYNC1
0: Lock on trailing edge of HSYNC1 (default)
1: Lock on leading edge of HSYNC1
1
PLL Lock Edge
HSYNC2
0: Lock on trailing edge of HSYNC2 (default)
1: Lock on leading edge of HSYNC2
2
3
Reserved
Set to 0
CLKINV Pin
IN
Disable
0: CLKINV pin enabled (default)
IN
1: CLKINV pin disabled (internally forced low)
IN
5:4
CLKINV Pin
IN
Function
00: CLKINV (default)
01: External CLAMP (See Note)
10: External COAST
11: External PIXCLK
Note: the CLAMP pulse is used to
- perform a DC restore (if enabled)
- start the ABLC™ function (if enabled), and
- update the data to the Offset DACs (always).
In the default internal CLAMP mode, the ISL98001
automatically generates the CLAMP pulse. If External
CLAMP is selected, the Offset DAC values only
change on the leading edge of CLAMP. If there is no
internal clamp signal, there will be up to a 100ms
delay between when the PGA gain or offset DAC
register is written to, and when the PGA or offset DAC
is actually updated.
6
7
XCLK
0: XCLK
1: XCLK
= f
= f
(default)
OUT
OUT
OUT
CRYSTAL
CRYSTAL
Frequency
/2
Disable XCLK
0 = XCLK
1 = XCLK
enabled
OUT
OUT
OUT
is logic low
0x14
0x15
0x16
DC Restore and ABLC™ starting pixel
MSB (0x00)
4:0
DC Restore and
ABLC™ starting
pixel (MSB)
Pixel after HSYNC trailing edge to begin
IN
DC restore and ABLC™ functions. 13-bits.
Set this register to the first stable black pixel following
the trailing edge of HSYNC
.
IN
DC Restore and ABLC™ starting pixel LSB
(0x03)
7:0
7:0
DC Restore and
ABLC™ starting
pixel (LSB)
DC Restore Clamp Width
(0x10)
DC Restore clamp
width (pixels)
Width of DC restore clamp used in AC-coupled
configurations. Has no effect on ABLC™. Minimum
value is 0x02 (a setting of 0x01 or 0x00 will not
generate a clamp pulse).
0x17
ABLC™ Configuration (0x40)
0
ABLC™ disable
Reserved
0: ABLC™ enabled (default)
1: ABLC™ disabled
1
Set to 0.
3:2
ABLC™ pixel width Number of black pixels averaged every line for
ABLC™ function
00: 16 pixels [default]
01: 32 pixels
10: 64 pixels
11: 128 pixels
6:4
7
ABLC™ bandwidth
Reserved
ABLC™ Time constant (lines) = 2(5+[6:4])
000 = 32 lines
100 = 256 lines (default)
111 = 4096 lines
Set to 0.
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ISL98001
Register Listing (Continued)
ADDRESS
REGISTER (DEFAULT VALUE)
BIT(S) FUNCTION NAME
DESCRIPTION
0: 24-bits: Data output on R , G , B only; R , G , B
S
0x18
Output Format (0x00)
0
Bus Width
P
P
P
S
S
are all driven low (default).
1: 48-bits: Data output on R , R , G , G , B , B
S.
P
P
P
S
S
1
Interleaving
(48-bit mode only)
0: No interleaving: data changes on same edge of
DATACLK (default).
1: Interleaved: Secondary databus data changes on
opposite edge of DATACLK from primary databus.
2
Bus Swap
(48-bit mode only)
0: First data byte after trailing edge of HSOUT
appears on R , G , B (default).
P P P
1: First data byte after trailing edge of HSOUT
appears on R , G , B (primary and secondary
S
S
S
busses are reversed).
3
4
UV order
0: U0 V0 U2 V2 U4 V4 U6 V6… (default)
1: U0 V1 U2 V3 U4 V5 U6 V7… (X980xx)
(422 mode only)
422 mode
0: Data is formatted as 4:4:4 (RGB, default).
1: Data is decimated to 4:2:2 (YUV), blue channel is
driven low.
5
DATACLK
Polarity
0: HS
, VS
, and Pixel Data changes on falling
OUT
OUT
edge of DATACLK (default).
1: HS
edge of DATACLK.
, VS
, and Pixel Data changes on rising
OUT
OUT
6
7
VS
HS
HS
Polarity
Polarity
Width
0: Active High (default)
1: Active Low
OUT
OUT
OUT
0: Active High (default)
1: Active Low
0x19
0x1A
HS
Width (0x10)
7:0
HS
width, in pixels. Minimum value is 0x01 for 24-
OUT
OUT
bit modes, 0x02 for 48-bit modes.
Output Signal Disable (0x00)
0
1
2
3
4
5
6
Three-state R [7:0] 0 = Output byte enabled
P
1 = Output byte three-stated
Three-state R 7:0]
S
These bits override all other I/O settings
Output data pins have 56kΩ pulldown resistors to
Three-state G [7:0]
P
GND .
D
Three-state G 7:0]
S
Three-state B [7:0]
P
Three-state B [7:0]
S
Three-state
DATACLK
0 = DATACLK enabled
1 = DATACLK three-stated
7
0
1
2
3
Three-state
DATACLK
0 = DATACLK enabled
1 = DATACLK three-stated
0x1B
Power Control (0x00)
Red
Power-down
0 = Red ADC operational (default)
1 = Red ADC powered down
Green
Power-down
0 = Green ADC operational (default)
1 = Green ADC powered down
Blue
Power-down
0 = Blue ADC operational (default)
1 = Blue ADC powered down
PLL
Power-down
0 = PLL operational (default)
1 = PLL powered down
7:4
7:0
Reserved
Reserved
Set to 0.
0x1C
PLL Tuning (0x49)
Use default setting of 0x49 for all PC and video
modes except signals coming from an analog VCR.
Set to 0x4C for analog videotape compatibility.
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ISL98001
Register Listing (Continued)
ADDRESS
REGISTER (DEFAULT VALUE)
BIT(S) FUNCTION NAME
DESCRIPTION
0x1D
Red ABLC Target (0x00)
7:0
Reserved
This is a 2's complement number controlling the
target code of the Red ADC output when ABLC is
enabled.
In RGB mode, the Red ADC output will be servoed to
0x00 + the number in this register (-0x00 to +0x7F).
In YPbPr mode, the Red ADC output will be servoed
to 0x80 + the number in this register (-0x80 to +0x7F).
Note: This register does NOT disable the digital offset
adder. Both functions can be used simultaneously.
0x1E
0x1F
Green ABLC Target (0x00)
Blue ABLC Target (0x00)
7:0
7:0
Reserved
Reserved
This is a 2's complement number controlling the
target code of the Green ADC output when ABLC is
enabled.
In RGB and YPbPr modes, the Green ADC output will
be servoed to 0x00 + the number in this register
(-0x00 to +0x7F).
Note: This register does NOT disable the digital offset
adder. Both functions can be used simultaneously.
This is a 2's complement number controlling the
target code of the Blue ADC output when ABLC is
enabled.
In RGB mode, the Blue ADC output will be servoed to
0x00 + the number in this register (-0x00 to +0x7F).
In YPbPr mode, the Blue ADC output will be servoed
to 0x80 + the number in this register (-0x80 to +0x7F).
Note: This register does NOT disable the digital offset
adder. Both functions can be used simultaneously.
0x23
DC Restore Clamp (0x18)
3:0
6:4
Reserved
Set to 1000
DC Restore Clamp
Impedance
DC Restore clamp's ON resistance.
Shared for all three channels
0: Infinite (clamp disconnected) (default)
1: 1600Ω
2: 800Ω
3: 533Ω
4: 400Ω
5: 320Ω
6: 267Ω
7: 228Ω
7
Reserved
Set to 0.
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ISL98001
Register Listing (Continued)
ADDRESS
REGISTER (DEFAULT VALUE)
BIT(S) FUNCTION NAME
DESCRIPTION
, HSYNC , VS
0x25
Sync Separator Control (0x00)
0
Three-state Sync
Outputs
0: VSYNC
, HS
are
OUT
OUT
OUT
OUT
OUT
active (default).
1: VSYNC , HSYNC
, VS , HS
OUT
are in
OUT
OUT
three-state.
1
COAST Polarity
0: Coast active high (default)
1: Coast active low
Set to 0 for internal VSYNC extracted from CSYNC.
Set to 0 or 1 as appropriate to match external VSYNC
or external COAST.
2
HS
Lock Edge
0: HS
's trailing edge is locked to selected
OUT
OUT
HSYNC 's lock edge. Leading edge moves
IN
backward in time as HS
(X980xx default).
width is increased
OUT
1: HS
's leading edge is locked to selected
OUT
HSYNC 's lock edge. Trailing edge moves forward
IN
in time as HS
width is increased.
OUT
3
4
Reserved
VSYNC
Set to 0
Mode
0: VSYNC
is aligned to HSYNC
edge,
OUT
OUT
OUT
providing “perfect” VSYNC signal (default).
1: VSYNC
is “raw” integrator output.
OUT
5
6
7
Reserved
Reserved
Set to 0
Set to 0
VS
Mode
0: VS
is output on VS
pin (default).
OUT
OUT
OUT
1: COAST (including pre- and post-coast COAST) is
output on VS pin.
OUT
The ISL98001's DPLL has less than 250ps of jitter, peak to
peak, and independent of the pixel rate. The DPLL generates
64 phase steps per pixel (vs. the industry standard 32), for
fine, accurate positioning of the sampling point. The crystal-
locked NCO inside the DPLL completely eliminates drift due to
charge pump leakage, so there is inherently no frequency or
phase change across a line. An intelligent all-digital loop filter/
controller eliminates the need for the user to have to program
or change anything (except for the number of pixels) to lock
over a range from interlaced video (10MHz or higher) to
UXGA 60Hz (170MHz, with the ISL98001-170).
Technical Highlights
The ISL98001 provides all the features of traditional triple
channel video AFEs, but adds several next-generation
enhancements, bringing performance and ease of use to
new levels.
DPLL
All video AFEs must phase lock to an HSYNC signal,
supplied either directly or embedded in the video stream
(Sync On Green). Historically this has been implemented as
a traditional analog PLL. At SXGA and lower resolutions, an
analog PLL solution has proven adequate, if somewhat
troublesome (due to the need to adjust charge pump
currents, VCO ranges and other parameters to find the
optimum trade-off for a wide range of pixel rates).
The DPLL eliminates much of the performance limitations and
complexity associated with noise-free digitization of high
speed signals.
Automatic Black Level Compensation (ABLC™)
and Gain Control
As display resolutions and refresh rates have increased,
however, the pixel period has shrunk. An XGA pixel at a
60Hz refresh rate has 15.4ns to change and settle to its new
value. But at UXGA 75Hz, the pixel period is 4.9ns. Most
consumer graphics cards (even the ones with “350MHz”
DACs) spend most of that time slewing to the new pixel
value. The pixel may settle to its final value with 1ns or less
before it begins slewing to the next pixel. In many cases it
rings and never settles at all. So precision, low-jitter
sampling is a fundamental requirement at these speeds, and
a difficult one for an analog PLL to meet.
Traditional video AFEs have an offset DAC prior to the ADC,
to both correct for offsets on the incoming video signals and
add/subtract an offset for user “brightness control” without
sacrificing the 8-bit dynamic range of the ADC. This solution
is adequate, but it places significant requirements on the
system's firmware, which must execute a loop that detects
the black portion of the signal and then servos the offset
DACs until that offset is nulled (or produces the desired ADC
output code). Once this has been accomplished, the offset
(both the offset in the AFE and the offset of the video card
FN6148.0
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October 25, 2005
ISL98001
generating the signal) is subject to drift - the temperature
inside a monitor or projector can easily change 50°C
between power-on/offset calibration on a cold morning and
the temperature reached once the monitor and the monitor's
environment have reached steady state. Offset can drift
significantly over 50°C, reducing image quality and requiring
that the user do a manual calibration once the monitor has
warmed up.
Functional Description
Inputs
The ISL98001 digitizes analog video inputs in both RGB
and Component (YPbPr) formats, with or without
embedded sync (SOG).
RGB Inputs
For RGB inputs, the black/blank levels are identical and equal
to 0V. The range for each color is typically 0V to 0.7V from
black to white. HSYNC and VSYNC are separate signals.
In addition to drift, many AFEs exhibit interaction between
the offset and gain controls. When the gain is changed, the
magnitude of the offset is changed as well. This again
increases the complexity of the firmware as it tries to
optimize gain and offset settings for a given video input
signal. Instead of adjusting just the offset, then the gain, both
have to be adjusted interactively until the desired ADC
output is reached.
Component YPbPr Inputs
In addition to RGB and RGB with SOG, the ISL98001 has an
option that is compatible with the component YPbPr video
inputs typically generated by DVD players. While the
ISL98001 digitizes signals in these color spaces, it does not
perform color space conversion; if it digitizes an RGB signal,
it outputs digital RGB, while if it digitizes a YPbPr signal, it
outputs digital YCbCr, also called YUV.
The ISL98001 simplifies offset and gain adjustment and
completely eliminates offset drift using its Automatic Black
Level Compensation (ABLC™) function. ABLC™ monitors the
black level and continuously adjusts the ISL98001's 10-bit
offset DACs to null out the offset. Any offset, whether due to
the video source or the ISL98001's analog amplifiers, is
eliminated with 10-bit (1/4 of an ADC LSB) accuracy. Any drift
is compensated for well before it can have a visible effect.
Manual offset adjustment control is still available - an 8-bit
register allows the firmware to adjust the offset ±64 codes in
exactly 1 ADC LSB increments. And gain is now completely
independent of offset - adjusting the gain no longer affects the
offset, so there is no longer a need to program the firmware to
cope with interactive offset and gain controls.
The Luminance (Y) signal is applied to the Green Channel
and is processed in a manner identical to the Green input
with SOG described previously. The color difference signals
Pb and Pr are bipolar and swing both above and below the
black level. When the YPbPr mode is enabled, the black
level output for the color difference channels shifts to a mid
scale value of 0x80. Setting configuration register
0x05[2] = 1 enables the YPbPr signal processing mode of
operation.
TABLE 1. YUV MAPPING (4:4:4)
ISL98001
INPUT
ISL98001
OUTPUT
INPUT
OUTPUT
SIGNAL
Finally, there should be no concerns over ABLC™ itself
introducing visible artifacts; it doesn't. ABLC™ functions at a
very low frequency, changing the offset in 1/4 LSB
increments, so it can't cause visible brightness fluctuations.
And once ABLC™ is locked, if the offset doesn't drift, the
DACs won't change. If desired, ABLC™ can be disabled,
allowing the firmware to work in the traditional way, with
10-bit offset DACs under the firmware's control.
SIGNAL
CHANNEL
ASSIGNMENT
Y
Green
Blue
Green
Blue
Y Y Y Y
1 2 3
0
Pb
Pr
U U U U
0
1
2
3
3
Red
Red
V V V V
0 1 2
The ISL98001 can optionally decimate the incoming data to
provide a 4:2:2 output stream (configuration register
0x18[4] = 1) as shown in Table 2.
Gain and Offset Control
To simplify image optimization algorithms, the ISL98001
features fully-independent gain and offset adjustment.
Changing the gain does not affect the DC offset, and the
weight of an Offset DAC LSB does not vary depending on
the gain setting.
TABLE 2. YUV MAPPING (4:2:2)
ISL98001
INPUT
ISL98001
OUTPUT
INPUT
OUTPUT
SIGNAL
SIGNAL
CHANNEL
ASSIGNMENT
Y
Green
Blue
Green
Blue
Y Y Y Y
0 1 2 3
The full-scale gain is set in the three 8-bit registers
Pb
Pr
driven low
U V U V
0 0 2 2
(0x06-0x08). The ISL98001 can accept input signals with
amplitudes ranging from 0.35V
to 1.4V
.
Red
Red
P-P
P-P
The offset controls shift the entire RGB input range, changing
the input image brightness. Three separate registers provide
independent control of the R, G, and B channels. Their
nominal setting is 0x80, which forces the ADC to output code
0x00 (or 0x80 for the R (Pr) and B (Pb) channels in YPbPr
mode) during the back porch period when ABLC™ is enabled.
There is also a “compatibility mode”, enabled by setting bit 3
of register 0x18 to a 1, that outputs the U and V data with the
format used by the previous generation (“X980xx”) series of
AFEs, shown in Table 3.
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October 25, 2005
ISL98001
Automatic Black Level
Compensation (ABLC™) Loop
DC Restoration
Offset
10
Fixed
Offset
Control
To
CLAMP
Offset
DAC
Registers
10
ABLC
Block
GENERATION
0x00
8
VCLAMP
8
DC Restore
Clamp DAC
10
ABLC™
ABLC™
Fixed
Offset
ABLC™
R(GB)IN
1
8
VIN
+
VGA1
VGA2
R(GB)GND1
Input
8
8
To Output
Formatter
PGA
8 bit ADC
Bandwidth
VIN
-
R(GB)IN
2
Bandwidth
Control
R(GB)GND2
FIGURE 7. VIDEO FLOW (INCLUDING ABLC™)
SOG
TABLE 3. YUV MAPPING (4:2:2)
For component YPbPr signals, the sync signal is embedded
on the Y channel’s video, which is connected to the green
input, hence the name SOG (Sync on Green). The horizontal
sync information is encoded onto the video input by adding
the sync tip during the blanking interval. The sync tip level is
typically 0.3V below the video black level.
ISL98001
INPUT
ISL98001
OUTPUT
INPUT
OUTPUT
SIGNAL
SIGNAL
CHANNEL
ASSIGNMENT
Y
Green
Blue
Green
Blue
Y Y Y Y
1 2 3
0
Pb
Pr
driven low
U V U V
1 2 3
To minimize the loading on the green channel, the SOG input
for each of the green channels should be AC-coupled to the
ISL98001 through a series combination of a 10nF capacitor
and a 500Ω resistor. Inside the ISL98001, a window
Red
Red
0
Input Coupling
Inputs can be either AC-coupled (default) or DC-coupled (See
register 0x05[1]). AC coupling is usually preferred since it
allows video signals with substantial DC offsets to be accurately
digitized. The ISL98001 provides a complete internal
DC-restore function, including the DC restore clamp (See
Figure 7) and programmable clamp timing (registers 0x14,
0x15, 0x16, and 0x23).
comparator compares the SOG signal with an internal 4-bit
programmable threshold level reference ranging from 0mV to
300mV below the minimum sync level. The SOG threshold
level, hysteresis, and low-pass filter is programmed via
register 0x04. If the Sync-On-Green function is not needed,
the SOG pin(s) may be left unconnected.
IN
SYNC Processing
When AC-coupled, the DC restore clamp is applied every line,
a programmable number of pixels after the trailing edge of
HSYNC. If register 0x05[5] = 0 (the default), the clamp will not
be applied while the DPLL is coasting, preventing any clamp
voltage errors from composite sync edges, equalization pulses,
or Macrovision signals.
The ISL98001 can process sync signals from 3 different
sources: discrete HSYNC and VSYNC, composite sync on
the HSYNC input, or composite sync from a Sync-On-Green
(SOG) signal embedded on the Green video input. The
ISL98001 has SYNC activity detect functions to help the
firmware determine which sync source is available.
After the trailing edge of HSYNC, the DC restore clamp is
turned on after the number of pixels specified in the DC Restore
and ABLC™ Starting Pixel registers (0x14 and 0x15) has been
reached. The clamp is applied for the number of pixels
specified by the DC Restore Clamp Width Register (0x16). The
clamp can be applied to the back porch of the video, or to the
front porch (by increasing the DC Restore and ABLC™ Starting
Pixel registers so all the active video pixels are skipped).
Macrovision
The ISL98001 automatically detects the presence of
Macrovision-encoded video. When Macrovision is detected,
it generates a mask signal that is ANDed with the incoming
SOG CSYNC signal to remove the Macrovision before the
HSYNC goes to the PLL. No additional programming is
required to support Macrovision.
If DC-coupled operation is desired, the input to the ADC will be
If desired (it is never necessary in normal operation), this
function can be disabled by setting the Sync Mask Disable
(register 0x05 bit 6) to a 1.
the difference between the input signal (R 1, for example) and
IN
that channel’s ground reference (RGB
1 in that example).
GND
FN6148.0
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October 25, 2005
ISL98001
The mask signal is also applied to the HSYNC
signal.
to the correct value before the next headswitch, rendering
OUT
When Sync Mask Disable = 0, any Macrovision present on
the incoming sync will not be visible on HSYNC . If the
the image completely unintelligible.
OUT
Intersil’s DPLL has the capability to correct large phase
changes almost instantly by maximizing the phase error gain
while keeping the frequency gain relatively low. This is done
by changing the contents of register 0x1C to 0x4C. This
increases the phase error gain to 100%. Because a phase
setting this high will slightly increase jitter, the default setting
(0x49) for register 0x1C is recommended for all other sync
sources.
application requires the Macrovision pulses to be visible on
HSYNC , set the HSYNC Mask Disable bit (register
OUT
OUT
0x05 bit 7).
Headswitching from Analog Videotape Signals
Occasionally this AFE may be used to digitize signals
coming from analog videotape sources. The most common
example of this is a Digital VCR (which for best signal quality
would be connected to this AFE with a component YPbPr
connection). If the digital VCR is playing an older analog
VHS tape, the sync signals from the VCR may contain the
worst of the traditional analog tape artifacts: headswitching.
Headswitching is traditionally the enemy of PLLs with large
capture ranges, because a headswitch can cause the
HSYNC period to change by as much as ±90%. To the PLL,
this can look like a frequency change of -50% to greater than
+900%, causing errors in the output frequency (and
PGA
The ISL98001’s Programmable Gain Amplifier (PGA) has a
nominal gain range from 0.5V/V (-6dB) to 2.0V/V (+6dB).
The transfer function is:
V
---
GainCode
Gain
= 0.5 + ----------------------------
V
170
where GainCode is the value in the Gain register for that
particular color. Note that for a gain of 1V/V, the GainCode
should be 85 (0x55). This is a different center value than the
128 (0x80) value used by some other AFEs, so the firmware
should take this into account when adjusting gains.
obviously the phase) to change. Subsequent HSYNCs have
the correct, original period, but most analog PLLs will take
dozens of lines to settle back to the correct frequency and
phase after a headswitch disturbance. This causes the top of
the image to “tear” during normal playback. In “trick modes”
(fast forward and rewind), the HSYNC signal has multiple
headswitch-like discontinuities, and many PLLs never settle
The PGAs are updated by the internal clamp signal once per
line. In normal operation this means that there is a maximum
ACTIVITY 0x01[6:0]
&
POLARITY 0x02[5:0]
DETECT
HSYNC1
HSYNCOUT
CSYNC
HSYNCIN
1
1
SLICER
SOURCE
0x03[2:0]
0:
00, 10,
11:
SYNC
TYPE
VSYNCIN
HSYNCIN
VGA1
HSYNCIN
SOG
SLICER
0x1C
VSYNC
SYNC
SOGIN1
1:
0x05[4:3]
SPLITTER
SYNC
SPLTR
SOGIN
0x05[0]
HSYNC2
SLICER
0x03[6:4]
01:
HSYNCIN
2
VSYNCOUT
SOGIN
0x05[3]
VSYNCIN
1:
0:
VSYNCIN2
SOGIN
VGA2
VSYNCIN
SOG
SLICER
0x1C
2
COAST
RP[7:0]
RS[7:0]
GP[7:0]
GENERATION
0x11, 0x12, 0x13[2]
Pixel Data
from AFE
24
CLOCKINVIN
GS[7:0]
BP[7:0]
Output
HS
Formatter
PLL
BS[7:0]
XTALIN
0x18,
0x19,
0x1A
0x0E through 0x13
DATACLK
DATACLK
PIXCLK
0: ÷1
XTALOUT
0x13
[6]
HSOUT
VSOUT
1: ÷2
÷2
XTALCLOCKOUT
FIGURE 8. SYNC FLOW
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21
ISL98001
delay of one HSYNC period between a write to a Gain
When the ABLC function is enabled (0x17[0] = 0), the ABLC
function is executed every line after the trailing edge of
HSYNC. If register 0x05[5] = 0 (the default), the ABLC
function will be not be triggered while the DPLL is coasting,
preventing any composite sync edges, equalization pulses,
or Macrovision signals from corrupting the black data and
potentially adding a small error in the ABLC accumulator.
register for a particular color and the corresponding change
in that channel’s actual PGA gain. If there is no regular
HSYNC/SOG source, or if the external clamp option is
enabled (register 0x13[5:4]) but there is no external clamp
signal being generated, it may take up to 100ms for a write
to the Gain register to update the PGA. This is not an issue
in normal operation with RGB and YPbPr signals.
After the trailing edge of HSYNC, the start of ABLC is
delayed by the number of pixels specified in registers 0x14
and 0x15. After that delay, the number of pixels specified
by register 0x17[3:2] are averaged together and added to
the ABLC’s accumulator. The accumulator stores the
average black levels for the number of lines specified by
register 0x17[6:4], which is then used to generate a 10-bit
DAC value.
Offset DAC
The ISL98001 features a 10-bit Digital-to-Analog Converter
(DAC) to provide extremely fine control over the full channel
offset. The DAC is placed after the PGA to eliminate
interaction between the PGA (controlling “contrast”) and the
Offset DAC (controlling “brightness”).
In normal operation, the Offset DAC is controlled by the
ABLC™ circuit, ensuring that the offset is always reduced
to sub-LSB levels (See the following ABLC™ section for
more information). When ABLC™ is enabled, the Offset
registers (0x09, 0x0A, 0x0B) control a digital offset added
to or subtracted from the output of the ADC. This mode
provides the best image quality and eliminates the need for
any offset calibration.
The default values provide excellent results with offset
stability and absolute accuracy better than 1 ADC LSB for
most input signals.
ADC
The ISL98001 features 3 fully differential, high-speed 8-bit
ADCs.
Clock Generation
If desired, ABLC™ can be disabled (0x17[0] = 1) and the
Offset DAC programmed manually, with the 8 most
significant bits in registers 0x09, 0x0A, 0x0B, and the 2 least
significant bits in register 0x0C[7:2].
A Digital Phase Lock Loop (DPLL) is employed to generate
the pixel clock frequency. The HSYNC input and the external
XTAL provide a reference frequency to the PLL. The PLL
then generates the pixel clock frequency that equal to the
incoming HSYNC frequency times the HTOTAL value
programmed into registers 0x0E and 0x0F.
The default Offset DAC range is ±127 ADC LSBs. Setting
0x0C[0] = 1 reduces the swing of the Offset DAC by 50%,
making 1 Offset DAC LSB the weight of 1/8th of an ADC
LSB. This provides the finest offset control and applies to
both ABLC™ and manual modes.
The stability of the clock is very important and correlates
directly with the quality of the image. During each pixel time
transition, there is a small window where the signal is
slewing from the old pixel amplitude and settling to the new
pixel value. At higher frequencies, the pixel time transitions
at a faster rate, which makes the stable pixel time even
smaller. Any jitter in the pixel clock reduces the effective
stable pixel time and thus the sample window in which pixel
sampling can be made accurately.
Automatic Black Level Compensation (ABLC™)
ABLC is a function that continuously removes all offset
errors from the incoming video signal by monitoring the
offset at the output of the ADC and servoing the 10-bit
analog DAC to force those errors to zero. When ABLC is
enabled, the user offset control is a digital adder, with 8-bit
resolution (See Table 4).
TABLE 4. OFFSET DAC RANGE AND OFFSET DAC ADJUSTMENT
OFFSET
DAC RANGE
0X0C[0]
10-BIT
USER OFFSET CONTROL RESOLUTION
USING REGISTERS 0x09 - 0X0B ONLY
(8-BIT OFFSET CONTROL)
USER OFFSET CONTROL RESOLUTION
USING REGISTERS 0X09 - 0x0B AND
0X0C[7:2](10-BIT OFFSET CONTROL)
OFFSET DAC
RESOLUTION
ABLC™
0x17[0]
0
1
0
1
0.25 ADC LSBs
(0.68mV)
0
1 ADC LSB
N/A
(ABLC on)
(digital offset control)
0.125 ADC LSBs
(0.34mV)
0
1 ADC LSB
(digital offset control)
N/A
(ABLC on)
0.25 ADC LSBs
(0.68mV)
1
1.0 ADC LSB
(analog offset control)
0.25 ADC LSB
(analog offset control)
(ABLC off)
0.125 ADC LSBs
(0.34mV)
1
0.5 ADC LSB
(analog offset control)
0.125 ADC LSB
(analog offset control)
(ABLC off)
FN6148.0
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22
ISL98001
The accuracy of the Trilevel Sync detect bit can be increased
Sampling Phase
The ISL98001 provides 64 low-jitter phase choices per pixel
period, allowing the firmware to precisely select the optimum
sampling point. The sampling phase register is 0x10.
by multiple reads of the Trilevel Sync detect bit. See the
Trilevel Sync Detect section for more details.
For best SOG operation, the SOG low pass filter (register
0x04[4] should always be enabled to reject the high
frequency peaking often seen on video signals.
HSYNC Slicer
To further minimize jitter, the HSYNC inputs are treated as
analog signals, and brought into a precision slicer block with
thresholds programmable in 400mV steps with 240mV of
hysteresis, and a subsequent digital glitch filter that ignores
any HSYNC transitions within 100ns of the initial transition.
This processing greatly increases the AFE’s rejection of
ringing and reflections on the HSYNC line and allows the
AFE to perform well even with pathological HSYNC signals.
HSYNC and VSYNC Activity Detect
Activity on these bits always indicates valid sync pulses, so
they should have the highest priority and be used even if the
SOG activity bit is also set.
SOG Activity Detect
The SOG activity detect bit monitors the output of the SOG
slicer, looking for 64 consecutive pulses with the same period
and duty cycle. If there is no signal on the Green (or Y)
channel, the SOG slicer will clamp the video to a DC level and
will reject any sporadic noise. There should be no false
positive SOG detects if there is no video on Green (or Y).
Voltages given above and in the HSYNC Slicer register
description are with respect to a 3.3V sync signal at the
HSYNC input pin. To achieve 5V compatibility, a 680Ω
IN
series resistor should be placed between the HSYNC source
and the HSYNC input pin. Relative to a 5V input, the
IN
hysteresis will be 240mV*5V/3.3V = 360mV, and the slicer
step size will be 400mV*5V/3.3V = 600mV per step.
If there is video on Green (or Y) with no valid SOG signal,
the SOG activity detect bit may sometimes report false
positives (it will detect SOG when no SOG is actually
present). This is due to the presence of video with a
repetitive pattern that creates a waveform similar to SOG.
For example, the desktop of a PC operating system is black
during the front porch, horizontal sync, and back porch, then
increases to a larger value for the video portion of the
screen. This creates a repetitive video waveform very similar
to SOG that may falsely trigger the SOG Activity detect bit.
However, in these cases where there is active video without
SOG, the SYNC information will be provided either as
SOG Slicer
The SOG input has programmable threshold, 40mV of
hysteresis, and an optional low pass filter that can be used to
remove high frequency video spikes (generated by overzealous
video peaking in a DVD player, for example) that can cause
false SOG triggers. The SOG threshold sets the comparator
threshold relative to the sync tip (the bottom of the SOG pulse).
SYNC Status and Polarity Detection
The SYNC Status register (0x01) and the SYNC Polarity
register (0x02) continuously monitor all 6 sync inputs
separate H and V sync on HSYNC and VSYNC , or
IN
IN
composite sync on HSYNC . HSYNC and VSYNC
IN
IN
IN
(VSYNC , HSYNC , and SOG for each of 2 channels)
IN
IN
IN
should therefore be used to qualify SOG. The SOG Active bit
should only be considered valid if HSYNC Activity
Detect = 0. Note: Some pattern generators can output
HSYNC and SOG simultaneously, in which case both the
HSYNC and the SOG activity bits will be set, and valid. Even
in this case, however, the monitor should still choose
HSYNC over SOG.
and report their status. However, accurate sync activity
detection is always a challenge. Noise and repetitive video
patterns on the Green channel may look like SOG activity
when there actually is no SOG signal, while non-standard
SOG signals and trilevel sync signals may have amplitudes
below the default SOG slicer levels and not be easily
detected. As a consequence, not all of the activity detect bits
in the ISL98001 are correct under all conditions.
TriLevel Sync Detect
Unlike SOG detect, the TriLevel Sync detect function does
not check for 64 consecutive trilevel pulses in a row, and is
therefore less robust than the SOG detect function. It will
report false positives for SOG-less video for the same
reasons the SOG activity detect does, and should therefore
be qualified with both HSYNC and SOG. TriLevel Sync
Detect should only be considered valid if HSYNC Activity
Detect = 0 and SOG Activity Detect = 1.
Table 5 shows how to use the SYNC Status register (0x01)
to identify the presence of and type of a sync source. The
firmware should go through the table in the order shown,
stopping at the first entry that matches the activity indicators
in the SYNC Status register.
Final validation of composite sync sources (SOG or
Composite sync on HSYNC) should be done by setting the
Input Configuration register (0x05) to the composite sync
source determined by this table, and confirming that the
CSYNC detect bit is set.
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ISL98001
TABLE 5. SYNC SOURCE DETECTION TABLE
HSYNC
VSYNC
SOG
TRILEVEL
DETECT
DETECT
DETECT
DETECT
RESULT
1
1
1
0
X
X
X
X
Sync is on HSYNC and VSYNC
Sync is composite sync on HSYNC. Set Input configuration register to CSYNC on
HSYNC and confirm that CSYNC detect bit is set.
0
0
1
0
Sync is composite sync on SOG. It is possible that trilevel sync is present but amplitude
is too low to set trilevel detect bit. Use video mode table to determine if this video mode
is likely to have trilevel sync, and set clamp start, width values appropriately if it is.
0
0
0
0
1
0
1
Sync is composite sync on SOG. Sync is likely to be trilevel.
No valid sync sources on any input.
X
If there is a SOG signal, the TriLevel Detect bit will operate
detection. HSYNC
sync signal: either horizontal or composite sync. If a SOG input
is selected, HSYNC will output the entire SOG signal,
including the VSYNC portion, pre-/post-equalization pulses if
present, and Macrovision pulses if present. HSYNC
will be the same format as the incoming
OUT
correctly for standard trilevel sync levels (600mV ). In
P-P
some real-world situations, the peak-to-peak sync amplitude
OUT
may be significantly smaller, sometimes 300mV
or less.
P-P
In these cases the sync slicer will continue to operate
correctly, but the TriLevel Detect bit may not be set. Trilevel
detection accuracy can be enhanced by polling the trilevel
bit multiple times. If HSYNC is inactive, SOG is present, and
the TriLevel Sync Detect bit is read as a 1, there is a high
likelihood there is trilevel sync.
OUT
remains active when the ISL98001 is in power-down mode.
HSYNC is generally used for mode detection.
OUT
VSYNC
OUT
VSYNC
is an unmodified, buffered version of the
OUT
incoming VSYNC signal of the selected channel, with the
IN
CSYNC Present
original VSYNC period, polarity, and width to aid in mode
detection. If a SOG input is selected, this signal will output
the VSYNC signal extracted by the ISL98001’s sync slicer.
Extracted VSYNC will be the width of the embedded VSYNC
pulse plus pre- and post-equalization pulses (if present).
Macrovision pulses from an NTSC DVD source will lengthen
the width of the VSYNC pulse. Macrovision pulses from
other sources (PAL DVD or videotape) may appear as a
second VSYNC pulse encompassing the width of the
Macrovision. See the Macrovision section for more
information. VSYNC
function) remains active in power-down mode. VSYNC
is generally used for mode detection, start of field detection,
and even/odd field detection.
If a composite sync source (either CSYNC on HSYNC or
SOG) is selected through bits 3 and 4 of register 0x05, the
CSYNC Present bit in register 0x01 should be set. CSYNC
Present detects the presence of a low frequency, repetitive
signal inside HSYNC, which indicates a VSYNC signal. The
CSYNC Present bit should be used to confirm that the signal
being received is a reliable composite sync source.
SYNC Output Signals
The ISL98001 has 2 pairs of HSYNC and VSYNC output
(including the sync separator
OUT
signals, HSYNC
and VSYNC
, and HS
and
OUT
OUT
OUT
OUT
VS
.
OUT
HSYNC
and VSYNC
are buffered versions of the
OUT
OUT
incoming sync signals; no synchronization is done. These
signals are used for mode detection
HS
OUT
HS
is generated by the ISL98001’s control logic and is
OUT
HS
and VS
are generated by the ISL98001’s logic
OUT
synchronized to the output DATACLK and the digital pixel
data on the output databus. Its trailing edge is aligned with
pixel 0. Its width, in units of pixels, is determined by register
0x19, and its polarity is determined by register 0x18[7]. As
the width is increased, the trailing edge stays aligned with
pixel 0, while the leading edge is moved backwards in time
OUT
and are synchronized to the output DATACLK and the digital
pixel data on the output databus. HS is used to signal
OUT
the start of a new line of digital data. VS
most applications.
is not needed in
OUT
Both HSYNC
and VSYNC
(including the sync
OUT
OUT
relative to pixel 0. HS
start of a new line of pixels.
is used by the scaler to signal the
OUT
separator function) remain active in power-down mode. This
allows them to be used in conjunction with the Sync Status
registers to detect valid video without powering up the
ISL98001.
The HS Width register (0x19) controls the width of the
OUT
HS
pulse. The pulse width is nominally 1 pixel clock
OUT
period times the value in this register. In the 48 bit output
mode (register 0x18[0] = 1), or the YPbPr input mode
(register 0x05[2] = 1), the HS
pixel clock (1 DATACLK) increments (See Table 6).
HSYNC
OUT
is an unmodified, buffered version of the incoming
HSYNC
OUT
width is incremented in 2
OUT
HSYNC or SOG signal of the selected channel, with the
IN
IN
incoming signal’s period, polarity, and width to aid in mode
FN6148.0
October 25, 2005
24
ISL98001
22Ω. If the databus is heavily loaded (long traces, many other
part on the same bus), this value may need to be reduced. If
the databus is lightly loaded, it may be increased.
TABLE 6. HS
WIDTH
OUT
HS
WIDTH (PIXEL CLOCKS)
OUT
REGISTER
24-BIT MODE, 24-BIT MODE,
ALL 48-BIT
MODES
Intersil’s recommendations to minimize EMI are:
• Minimize the databus trace length
0x19 VALUE
RGB
YPbPr
0
1
2
3
4
5
6
7
0
1
2
3
4
5
6
7
1
1
3
3
5
5
7
7
0
0
2
2
4
4
6
6
• Minimize the databus capacitive loading.
If EMI is a problem in the final design, increase the value of the
digital output series resistors to reduce slew rates on the bus.
This can only be done as long as the scaler’s setup and hold
timing requirements continue to be met.
Reducing Power Dissipation
It is possible to reduce the total power consumption of the
ISL98001 in applications where power is a concern. There are
several techniques that can be used to reduce power
consumption:
VS
OUT
VS
is generated by the ISL98001’s control logic and is
OUT
• Internal Digital Voltage Regulator. The ISL98001 features
synchronized to the output DATACLK and the digital pixel
data on the output databus. Its leading and trailing edges are
aligned with pixel 7 (8 pixels after HSYNC trailing edge). Its
width, in units of lines, is equal to the width of the incoming
a 3.3V to 1.9V voltage regulator (pins VREG and
IN
VREG
) for the low voltage digital supply. This regulator
OUT
typically sources 100mA at 1.9V, dissipating up to 140mW in
heat. Providing an external, clean 1.8V supply to the V
,
CORE
VSYNC (See the VSYNC
description). Its polarity is
OUT
V
, and V
will substantially reduce power
PLL
COREADC
determined by register 0x18[6]. This output is not needed in
dissipation. The external 1.8V supply should ramp up after
most applications. Intersil strongly discourages using this
(or at the same time as) the digital 3.3V (V ) supply.
D
signal - use VSYNC
instead.
OUT
• Internal Analog Voltage Regulator. The ISL98001 also
features a 3.3V to 1.9V voltage regulator for the low voltage
Crystal Oscillator
analog supply. This voltage appears on the V
pins.
BYPASS
An external 22MHz to 27MHz crystal supplies the low-jitter
reference clock to the DPLL. The absolute frequency of this
crystal within this range is unimportant, as is the crystal’s
temperature coefficient, allowing use of less expensive,
lower-grade crystals.
Unlike the digital low voltage supply, there are no “in” and
“out” connections for this regulator. However, this internal
regulator can only source voltage, and can be effectively
bypassed by driving the V
pins with an external, clean
BYPASS
2.0V supply. The external 2.0V supply should ramp up after
(or at the same time as) the analog 3.3V (V ) supply.
A
As an alternative to a crystal, the XTAL pin can be driven
IN
• Buffering Digital Outputs. Switching 24 or 48 data output
pins into a capacitive bus can consume significant current.
The higher the capacitance on the external databus, the
higher the switching current. To minimize current
consumption inside the ISL98001, minimize bus capacitance
and/or insert data buffers such as the SN64AVC16827
between the ISL98001’s data outputs and the external
databus.
with a 3.3V CMOS-level external clock source at any
frequency between 22MHz and 33.5MHz. The ISL98001’s
jitter specification assumes a low-jitter crystal source. If the
external clock source has increased jitter, the sample clock
generated by the DPLL may exhibit increased jitter as well.
EMI Considerations
There are two possible sources of EMI on the ISL98001:
• Internal Reference Frequency. The crystal frequency is
multiplied by the value in register 0x2B to generate an
internal high frequency reference clock. This internal
frequency should be set to 400MHz ±10% for minimum
power consumption. For example, for a 33MHz frequency at
Crystal oscillator. The EMI from the crystal oscillator is
negligible. This is due to an amplitude-regulated, low voltage
sine wave oscillator circuit, instead of the typical high-gain
square wave inverter-type oscillator, so there are no harmonics.
The crystal oscillator is not a significant source of EMI.
XTAL , register 0x2B should be set to a value of 0x0C to
IN
minimize power.
Digital output switching. This is the largest potential source of
EMI. However, the EMI is determined by the PCB layout and
the loading on the databus. The way to control this is to put
series resistors on the output of all the digital pins (as our demo
board and reference circuits show). These resistors should be
as large as possible, while still meeting the setup and hold
timing requirements of the scaler. We recommend starting with
Standby Mode
The ISL98001 can be placed into a low power standby mode
by writing a 0x0F to register 0x1B, powering down the triple
ADCs, the DPLL, and most of the internal clocks.
FN6148.0
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ISL98001
To allow input monitoring and mode detection during power-
The ISL98001 has a 7-bit address on the serial bus. The
upper 6-bits are permanently set to 100110, with the lower
bit determined by the state of pin 48. This allows two
ISL98001s to be independently controlled while sharing the
same bus.
down, the following blocks remain active:
• Serial interface (including the crystal oscillator) to enable
register read/write activity
• Activity and polarity detect functions (registers 0x01 and
0x02)
The bus is nominally inactive, with SDA and SCL high.
Communication begins when the host issues a START
command by taking SDA low while SCL is high (Figure 9).
The ISL98001 continuously monitors the SDA and SCL lines
for the start condition and will not respond to any command
until this condition has been met. The host then transmits the
7-bit serial address plus a R/W bit, indicating if the next
transaction will be a Read (R/W = 1) or a Write (R/W = 0). If
the address transmitted matches that of any device on the
bus, that device must respond with an ACKNOWLEDGE
(Figure 10).
• The HSYNC
detection)
and VSYNC
pins (for mode
OUT
OUT
Initialization
The ISL98001 initializes with default register settings for an
AC-coupled, RGB input on the VGA1 channel, with a 24-bit
output.
Reset
The ISL98001 has a Power On Reset (POR) function that
resets the chip to its default state when power is initially
applied, including resetting all the registers to their default
settings as described in the Register Listing. The external
RESET pin duplicates the reset function of the POR without
having to cycle the power supplies. The RESET pin does not
need to be used in normal operation and can be tied high.
Once the serial address has been transmitted and
acknowledged, one or more bytes of information can be
written to or read from the slave. Communication with the
selected device in the selected direction (read or write) is
ended by a STOP command, where SDA rises while SCL is
high (Figure 9), or a second START command, which is
commonly used to reverse data direction without
relinquishing the bus.
ISL98001 Serial Communication
Overview
The ISL98001 uses a 2-wire serial bus for communication
with its host. SCL is the Serial Clock line, driven by the host,
and SDA is the Serial Data line, which can be driven by all
devices on the bus. SDA is open drain to allow multiple
devices to share the same bus simultaneously.
Data on the serial bus must be valid for the entire time SCL
is high (Figure 11). To achieve this, data being written to the
ISL98001 is latched on a delayed version of the rising edge
of SCL. SCL is delayed and deglitched inside the ISL98001
for three crystal clock periods (120ns for a 25MHz crystal) to
eliminate spurious clock pulses that could disrupt serial
communication.
Communication is accomplished in three steps:
When the contents of the ISL98001 are being read, the SDA
line is updated after the falling edge of SCL, delayed and
deglitched in the same manner.
1) The Host selects the ISL98001 it wishes to communicate
with.
2) The Host writes the initial ISL98001 Configuration
Register address it wishes to write to or read from.
Configuration Register Write
Figure 12 shows two views of the steps necessary to write
one or more words to the Configuration Register.
3) The Host writes to or reads from the ISL98001’s
Configuration Register. The ISL98001’s internal address
pointer auto increments, so to read registers 0x00 through
0x1B, for example, one would write 0x00 in step 2, then
repeat step three 28 times, with each read returning the
next register value.
Configuration Register Read
Figure 13 shows two views of the steps necessary to read
one or more words from the Configuration Register.
SCL
SDA
Start
Stop
FIGURE 9. VALID START AND STOP CONDITIONS
FN6148.0
26
October 25, 2005
ISL98001
SCL from
Host
1
8
9
Data Output
from Transmitter
Data Output
from Receiver
Start
Acknowledge
FIGURE 10. ACKNOWLEDGE RESPONSE FROM RECEIVER
SCL
SDA
Data Change
FIGURE 11. VALID DATA CHANGES ON THE SDA BUS
Data Stable
Data Stable
Signals the beginning of serial I/O
ISL98001 Serial Bus Address Write
START Command
ISL98001 Serial Bus
R/W
This is the 7-bit address of the ISL98001 on the 2-wire bus. The
address is 0x4C if pin 48 is low, 0x4D if pin 48 is high. Shift this
value left to when adding the R/W bit.
A
0
0
1
1
0
0
1
(pin 48)
ISL98001 Register Address Write
This is the address of the ISL98001’s configuration register that
the following byte will be written to.
A7
D7
A6
D6
A5
D5
A4
D4
A3
D3
A2
D2
A1
D1
A0
D0
ISL98001 Register Data Write(s)
This is the data to be written to the ISL98001’s configuration register.
Note: The ISL98001’s Configuration Register’s address pointer auto
increments after each data write: repeat this step to write multiple
sequential bytes of data to the Configuration Register.
(Repeat if desired)
Signals the ending of serial I/O
STOP Command
S
T
A
R
T
S
T
Serial Bus
Address
Register
Address
Data
Write*
* The data write step may be repeated to write to the
ISL98001’s Configuration Register sequentially, beginning at
the Register Address written in the previous step.
Signals from
the Host
O
P
1 0 0 1 1 0A0 a a a a a a a a d d d d d d d d
SDA Bus
Signals from
the ISL98001
A
C
K
A
C
K
A
C
K
FIGURE 12. CONFIGURATION REGISTER WRITE
FN6148.0
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October 25, 2005
ISL98001
Signals the beginning of serial I/O
ISL98001 Serial Bus Address Write
START Command
ISL98001 Serial Bus
R/W
This is the 7-bit address of the ISL98001 on the 2-wire bus. The
address is 0x4C if pin 48 is low, 0x4D if pin 48 is high. R/W = 0,
indicating next transaction will be a write.
A
0
1
1
0
0
0
1
(pin 48)
ISL98001 Register Address Write
A7
A6
A5
A4
A3
A2
A1
A0
This sets the initial address of the ISL98001’s configuration
register for subsequent reading.
Ends the previous transaction and starts a new one
START Command
ISL98001 Serial Bus
R/W
ISL98001 Serial Bus Address Write
This is the 7-bit address of the ISL98001 on the 2-wire bus. The
address is 0x4C if pin 48 is low, 0x4D if pin 48 is high. R/W = 1,
indicating next transaction(s) will be a read.
A
1
1
1
0
0
0
1
(pin 48)
ISL98001 Register Data Read(s)
This is the data read from the ISL98001’s configuration register.
D7
D6
D5
D4
D3
D2
D1
D0
Note: The ISL98001’s Configuration Register’s address pointer
auto increments after each data read: repeat this step to read
multiple sequential bytes of data from the Configuration Register.
(Repeat if desired)
Signals the ending of serial I/O
STOP Command
R
E
S
S
T
A
R
T
S
T
A
R
T
Serial Bus
Address
Serial Bus
Register
Address
Data
Signals from
the Host
* The data read step may be repeated to read
from the ISL98001’s Configuration Register
sequentially, beginning at the Register
Address written in the two steps previous.
T
O
P
Address
Read*
A
C
K
1 0 0 1 1 0A0 a a a a a a a a
1 0 0 1 1 0A1
SDA Bus
Signals from
the ISL98001
A
C
K
A
C
K
A
C
K
d d d d d d d d
FIGURE 13. CONFIGURATION REGISTER READ
All Intersil U.S. products are manufactured, assembled and tested utilizing ISO9000 quality systems.
Intersil Corporation’s quality certifications can be viewed at www.intersil.com/design/quality
Intersil products are sold by description only. Intersil Corporation reserves the right to make changes in circuit design, software and/or specifications at any time without
notice. Accordingly, the reader is cautioned to verify that data sheets are current before placing orders. Information furnished by Intersil is believed to be accurate and
reliable. However, no responsibility is assumed by Intersil or its subsidiaries for its use; nor for any infringements of patents or other rights of third parties which may result
from its use. No license is granted by implication or otherwise under any patent or patent rights of Intersil or its subsidiaries.
For information regarding Intersil Corporation and its products, see www.intersil.com
FN6148.0
28
October 25, 2005
128-Lead Metric Quad Flat Pack (MQFP) Package
All dimensions in mm.
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