LT1028CS8#TR [Linear]
LT1028 - Ultra Low Noise Precision High Speed Op Amps; Package: SO; Pins: 8; Temperature Range: 0°C to 70°C;
| 型号： | LT1028CS8#TR |
| 厂家： | 
Linear |
| 描述： | LT1028 - Ultra Low Noise Precision High Speed Op Amps; Package: SO; Pins: 8; Temperature Range: 0°C to 70°C 放大器 光电二极管 |
| 文件： | 总28页 (文件大小：368K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
LT1028/LT1128
Ultralow Noise Precision
High Speed Op Amps
FeaTures
DescripTion
n
Voltage Noise
The LT®1028(gain of –1 stable)/LT1128(gain of +1 stable)
achieveanewstandardofexcellenceinnoiseperformance
with 0.85nV/√Hz 1kHz noise, 1.0nV/√Hz 10Hz noise. This
ultralow noise is combined with excellent high speed
specifications (gain-bandwidth product is 75MHz for
LT1028, 20MHz for LT1128), distortion-free output, and
true precision parameters (0.1µV/°C drift, 10µV offset
voltage, 30 million voltage gain). Although the LT1028/
LT1128 input stage operates at nearly 1mA of collector
current to achieve low voltage noise, input bias current
is only 25nA.
1.1nV/√Hz Max at 1kHz
0.85nV/√Hz Typ at 1kHz
1.0nV/√Hz Typ at 10Hz
35nV Typ, 0.1Hz to 10Hz
P-P
n
n
Voltage and Current Noise 100% Tested
Gain-Bandwidth Product
LT1028: 50MHz Min
LT1128: 13MHz Min
Slew Rate
n
LT1028: 11V/µs Min
LT1128: 5V/µs Min
Offset Voltage: 40µV Max
Drift with Temperature: 0.8µV/°C Max
Voltage Gain: 7 Million Min
Available in 8-Lead SO Package
The LT1028/LT1128’s voltage noise is less than the noise
of a 50Ω resistor. Therefore, even in very low source
impedance transducer or audio amplifier applications,
the LT1028/LT1128’s contribution to total system noise
will be negligible.
n
n
n
n
L, LT, LTC, LTM, Linear Technology and the Linear logo are registered trademarks of Linear
Technology Corporation. All other trademarks are the property of their respective owners.
applicaTions
n
Low Noise Frequency Synthesizers
n
High Quality Audio
n
Infrared Detectors
n
Accelerometer and Gyro Amplifiers
n
350Ω Bridge Signal Conditioning
n
Magnetic Search Coil Amplifiers
n
Hydrophone Amplifiers
Typical applicaTion
Ultralow Noise 1M TIA Photodiode Amplifier
Voltage Noise vs Frequency
10
V
T
= 15V
S
0.1µF
4.32k
= 25°C
+
A
V
S
MAXIMUM
1M
1/f CORNER = 14Hz
D
S
JFET
NXP
0.5pF
TYPICAL
1
BF862
PHOTO
DIODE
SFH213
–
+
1/f CORNER = 3.5Hz
V
= ~0.4V + I • 1M
PD
OUT
LT1028
1028 TA01
4.99k
–
V
S
V
= ±15V
S
–
V
S
0.1
0.1
1
10
1k
100
FREQUENCY (Hz)
1028 TA02
1028fb
1
LT1028/LT1128
absoluTe MaxiMuM raTings
(Note 1)
Supply Voltage
Operating Temperature Range
–55°C to 105°C.................................................. 22V
105°C to 125°C.................................................. 16V
Differential Input Current (Note 9) ....................... 25mA
Input Voltage..............................Equal to Supply Voltage
Output Short-Circuit Duration.......................... Indefinite
LT1028/LT1128AM, M (OBSOLETE)... –55°C to 125°C
LT1028/LT1128AC, C (Note 11) ............–40°C to 85°C
Storage Temperature Range
All Devices......................................... –65°C to 150°C
Lead Temperature (Soldering, 10 sec.)..................300°C
pin conFiguraTion
TOP VIEW
V
TRIM
OS
8
TOP VIEW
+
1
3
V
V
TRIM
7
5
OS
V
OS
V
OS
1
2
3
4
8
7
6
5
–
TRIM
TRIM
6
OUT
–IN
2
+
–
+
–IN
V
+
OVER-
COMP
+IN
+IN
OUT
OVER-
COMP
4
V
–
V
–
(CASE)
S8 PACKAGE
8-LEAD PLASTIC SOIC
H PACKAGE
8-LEAD TO-5 METAL CAN
= 175°C, θ = 140°C/W, θ = 40°C/W
T
= 135°C, θ = 140°C/W
JMAX
JA
T
JMAX
JA
JC
OBSOLETE PACKAGE
TOP VIEW
TOP VIEW
V
V
NC
NC
1
2
3
4
5
6
7
8
16
15
14
NC
OS
OS
1
2
3
4
8
7
6
5
TRIM
TRIM
V+
NC
–
+
–IN
TRIM
–IN
TRIM
OUT
+IN
+
–
13
V
OVER-
COMP
–
V
+
+IN
12
OUT
OVER-
COMP
NC
NC
–
N8 PACKAGE
8-LEAD PLASTIC DIP
V
11
10
9
NC
NC
J8 PACKAGE
8-LEAD CERAMIC DIP
= 175°C, θ = 140°C/W, θ = 40°C/W
JA JC
SW PACKAGE
16-LEAD PLASTIC SOL
T
JMAX
T
= 140°C, θ = 130°C/W
JA
JMAX
OBSOLETE PACKAGE
NOTE: THIS DEVICE IS NOT RECOMMENDED FOR NEW DESIGNS
1028fb
2
LT1028/LT1128
orDer inForMaTion
LEAD FREE FINISH
LT1028ACN8#PBF
LT1028CN8#PBF
LT1128ACN8#PBF
LT1128CN8#PBF
LT1028CS8#PBF
LT1128CS8#PBF
LT1028CSW#PBF
TAPE AND REEL
PART MARKING*
LT1028ACN8
LT1028CN8
LT1128ACN8
LT1128CN8
1028
PACKAGE DESCRIPTION
8-Lead PDIP
SPECIFIED TEMPERATURE RANGE
0°C to 70°C
N/A
N/A
8-Lead PDIP
0°C to 70°C
N/A
8-Lead PDIP
0°C to 70°C
N/A
8-Lead PDIP
0°C to 70°C
LT1028CS8#TRPBF
LT1128CS8#TRPBF
LT1028CSW#TRPBF
8-Lead Plastic Small Outline
8-Lead Plastic Small Outline
16-Lead Plastic SOIC (Wide)
0°C to 70°C
1128
0°C to 70°C
LT1028CSW
0°C to 70°C
Consult LTC Marketing for parts specified with wider operating temperature ranges. *The temperature grade is identified by a label on the shipping container.
Consult LTC Marketing for information on nonstandard lead based finish parts.
For more information on lead free part marking, go to: http://www.linear.com/leadfree/
For more information on tape and reel specifications, go to: http://www.linear.com/tapeandreel/
elecTrical characTerisTics VS = 1ꢀVꢁ TA = 2ꢀ°C unless otherwise noted.
LT1028AM/AC
LT1128AM/AC
LT1028M/AC
LT1128M/AC
SYMBOL
PARAMETER
CONDITIONS
(Note 2)
MIN
TYP
10
MAX
MIN
TYP
20
MAX
UNITS
µV
V
Input Offset Voltage
40
80
OS
∆V
Long Term Input Offset
Voltage Stability
(Note 3)
0.3
0.3
µV/Mo
OS
∆Time
I
I
Input Offset Current
Input Bias Current
V
V
= 0V
= 0V
12
25
35
50
90
75
18
30
35
100
180
90
nA
nA
OS
B
CM
CM
e
Input Noise Voltage
Input Noise Voltage Density
0.1Hz to 10Hz (Note 4)
nV
P-P
n
f = 10Hz (Note 5)
1.00
0.85
1.7
1.1
1.0
0.9
1.9
1.2
nV/√Hz
nV/√Hz
O
f = 1000Hz, 100% Tested
O
I
n
Input Noise Current Density
f = 10Hz (Notes 4 and 6)
O
4.7
1.0
10.0
1.6
4.7
1.0
12.0
1.8
pA/√Hz
pA/√Hz
O
f = 1000Hz, 100% Tested
Input Resistance
Common Mode
Differential Mode
300
20
300
20
MΩ
kΩ
Input Capacitance
5
5
pF
V
Input Voltage Range
11.0
114
117
12.2
126
133
11.0
110
110
12.2
126
132
CMRR
PSRR
Common Mode Rejection Ratio
Power Supply Rejection Ratio
Large-Signal Voltage Gain
V
=
11V
dB
dB
CM
V = 4V to 18V
S
A
R ≥ 2k, V = 12V
7.0
5.0
3.0
30.0
20.0
15.0
5.0
3.5
2.0
30.0
20.0
15.0
V/µV
V/µV
V/µV
VOL
L
L
L
O
O
R ≥ 1k, V = 10V
R ≥ 600Ω, V = 10V
O
V
Maximum Output Voltage Swing
Slew Rate
R ≥ 2k
L
12.3
11.0
13.0
12.2
12.0
10.5
13.0
12.2
V
V
OUT
L
R ≥ 600Ω
SR
A
VCL
A
VCL
= –1
= –1
LT1028
LT1128
11.0
5.0
15.0
6.0
11.0
4.5
15.0
6.0
V/µs
V/µs
GBW
Gain-Bandwidth Product
f = 20kHz (Note 7)
O
LT1028
LT1128
50
13
75
20
50
11
75
20
MHz
MHz
O
f = 200kHz (Note 7)
Z
Open-Loop Output Impedance
Supply Current
V = 0, I = 0
80
80
Ω
O
O
O
I
S
7.4
9.5
7.6
10.5
mA
1028fb
3
LT1028/LT1128
elecTrical characTerisTics
The l denotes the specifications which apply over the operating
temperature range –ꢀꢀ°C ≤ TA ≤ 12ꢀ°C. VS = 1ꢀVꢁ unless otherwise noted.
LT1028AM
LT1128AM
LT1028M
LT1128M
SYMBOL
PARAMETER
CONDITIONS
(Note 2)
MIN
TYP
30
MAX
120
0.8
MIN
TYP
45
MAX
180
1.0
UNITS
µV
l
l
V
Input Offset Voltage
Average Input Offset Drift
OS
∆V
(Note 8)
0.2
0.25
µV/°C
OS
∆Temp
l
l
l
l
l
l
I
I
Input Offset Current
V
V
= 0V
= 0V
25
90
30
180
300
nA
nA
V
OS
B
CM
Input Bias Current
40
150
50
CM
Input Voltage Range
10.3
106
110
11.7
122
130
10.3
100
104
11.7
120
130
CMRR
PSRR
Common Mode Rejection Ratio
Power Supply Rejection Ratio
Large-Signal Voltage Gain
V
=
10.3V
dB
dB
CM
V = 4.5V to 16V
S
A
R ≥ 2k, V = 10V
R ≥ 1k, V = 10V
3.0
2.0
14.0
10.0
2.0
1.5
14.0
10.0
V/µV
V/µV
VOL
L
L
O
O
l
l
V
Maximum Output Voltage Swing
Supply Current
R ≥ 2k
L
10.3
11.6
8.7
10.3
11.6
9.0
V
OUT
I
11.5
13.0
mA
S
The l denotes the specifications which apply over the operating temperature range 0°C ≤ TA ≤ 70°C. VS = 1ꢀVꢁ unless otherwise
noted.
LT1028AC
LT1128AC
LT1028C
LT1128C
SYMBOL
PARAMETER
CONDITIONS
(Note 2)
MIN
TYP
15
MAX
80
MIN
TYP
30
MAX
125
1.0
UNITS
µV
l
l
V
OS
Input Offset Voltage
Average Input Offset Drift
∆V
(Note 8)
0.1
0.8
0.2
µV/°C
OS
∆Temp
l
l
l
l
l
l
I
I
Input Offset Current
V
V
= 0V
= 0V
15
65
22
130
240
nA
nA
V
OS
B
CM
Input Bias Current
30
120
40
CM
Input Voltage Range
10.5
110
114
12.0
124
132
10.5
106
107
12.0
124
132
CMRR
PSRR
Common Mode Rejection Ratio
Power Supply Rejection Ratio
Large-Signal Voltage Gain
V
CM
=
10.5V
dB
dB
V = 4.5V to 18V
S
A
R ≥ 2k, V = 10V
R ≥ 1k, V = 10V
5.0
4.0
25.0
18.0
3.0
2.5
25.0
18.0
V/µV
V/µV
VOL
L
L
O
O
l
l
V
Maximum Output Voltage Swing
Supply Current
R ≥ 2k
L
11.5
9.5
12.7
11.0
11.5
9.0
12.7
10.5
V
V
OUT
L
R ≥ 600Ω (Note 10)
I
8.0
10.5
8.2
11.5
mA
S
1028fb
4
LT1028/LT1128
elecTrical characTerisTics
The l denotes the specifications which apply over the operating
temperature range –40°C ≤ TA ≤ 8ꢀ°C. VS = 1ꢀVꢁ unless otherwise noted. (Note 11)
LT1028AC
LT1128AC
LT1028C
LT1128C
SYMBOL
PARAMETER
CONDITIONS
MIN
TYP
MAX
95
MIN
TYP
35
MAX
150
1.0
UNITS
µV
l
l
V
OS
Input Offset Voltage
Average Input Offset Drift
20
∆V
(Note 8)
0.2
0.8
0.25
µV/°C
OS
∆Temp
l
l
l
l
l
l
I
I
Input Offset Current
V
V
= 0V
= 0V
20
80
28
160
280
nA
nA
V
OS
B
CM
Input Bias Current
35
140
45
CM
Input Voltage Range
10.4
108
112
11.8
123
131
10.4
102
106
11.8
123
131
CMRR
PSRR
Common Mode Rejection Ratio
Power Supply Rejection Ratio
Large-Signal Voltage Gain
V
=
10.5V
dB
dB
CM
V = 4.5V to 18V
S
A
R ≥ 2k, V = 10V
R ≥ 1k, V = 10V
4.0
3.0
20.0
14.0
2.5
2.0
20.0
14.0
V/µV
V/µV
VOL
L
L
O
O
l
l
V
Maximum Output Voltage Swing
Supply Current
R ≥ 2k
L
11.0
12.5
8.5
11.0
12.5
8.7
V
OUT
I
11.0
12.5
mA
S
Note 1: Stresses beyond those listed under Absolute Maximum Ratings
may cause permanent damage to the device. Exposure to any Absolute
Maximum Rating condition for extended periods may affect device
reliability and lifetime.
Note 6: Current noise is defined and measured with balanced source
resistors. The resultant voltage noise (after subtracting the resistor noise
on an RMS basis) is divided by the sum of the two source resistors to
obtain current noise. Maximum 10Hz current noise can be inferred from
100% testing at 1kHz.
Note 2: Input Offset Voltage measurements are performed by automatic
test equipment approximately 0.5 sec. after application of power. In
Note 7: Gain-bandwidth product is not tested. It is guaranteed by design
and by inference from the slew rate measurement.
addition, at T = 25°C, offset voltage is measured with the chip heated
A
to approximately 55°C to account for the chip temperature rise when the
device is fully warmed up.
Note 3: Long Term Input Offset Voltage Stability refers to the average
Note 8: This parameter is not 100% tested.
Note 9: The inputs are protected by back-to-back diodes. Current-limiting
resistors are not used in order to achieve low noise. If differential input
voltage exceeds 1.8V, the input current should be limited to 25mA.
Note 10: This parameter guaranteed by design, fully warmed up at T
= 70°C. It includes chip temperature increase due to supply and load
currents.
trend line of Offset Voltage vs Time over extended periods after the first 30
days of operation. Excluding the initial hour of operation, changes in V
during the first 30 days are typically 2.5µV.
OS
A
Note 4: This parameter is tested on a sample basis only.
Note ꢀ: 10Hz noise voltage density is sample tested on every lot with the
exception of the S8 and S16 packages. Devices 100% tested at 10Hz are
available on request.
Note 11: The LT1028/LT1128 are designed, characterized and expected to
meet these extended temperature limits, but are not tested at –40°C and
85°C. Guaranteed I-grade parts are available. Consult factory.
1028fb
5
LT1028/LT1128
Typical perForMance characTerisTics
Wideband Voltage Noise
(0.1Hz to Frequency Indicated)
10Hz Voltage Noise Distribution
Wideband Noiseꢁ DC to 20kHz
180
160
140
120
100
80
10
1
V
T
=
1ꢀV
V
T
= 15V
S
A
S
A
158
148
= 2ꢀ°C
= 25°C
500 UNITS
MEASURED
FROM 4 RUNS
70
57
0.1
0.01
60
40
28
1028 G02
VERTICAL SCALE = 0.5µV/DIV
HORIZONTAL SCALE = 0.5ms/DIV
20
8
7
4
3
3
2
2
2
2
2
1
1
1
1
0
100
1k
10k
100k
1M
10M
0.8 1.0 1.2
1.4 1.6 1.8 2.0 2.2
VOLTAGE NOISE DENSITY (nV/√Hz)
0.6
BANDWIDTH (Hz)
1028 G03
1028 G01
Total Noise vs Matched Source
Resistance
Total Noise vs Unmatched Source
Resistance
Current Noise Spectrum
100
10
1
100
10
1
100
10
1
R
S
R
S
–
R
S
+
MAXIMUM
1/f CORNER = 800Hz
AT 10Hz
AT 1kHz
AT 1kHz
AT 10Hz
TYPICAL
2 R NOISE ONLY
S
2 R NOISE ONLY
S
1/f CORNER = 250Hz
V
=
1ꢀV
V
=
15V
S
A
S
A
T
= 2ꢀ°C
T
= 25°C
0.1
0.1
0.1
1
3
10 30 100 300 1k 3k 10k
1
3
10 30 100 300 1k 3k 10k
10
100
1k
10k
UNMATCHED SOURCE RESISTANCE (Ω)
FREQUENCY (Hz)
MATCHED SOURCE RESISTANCE (Ω)
1028 G05
1028 G04
1028 G06
0.1Hz to 10Hz Voltage Noise
0.01Hz to 1Hz Voltage Noise
Voltage Noise vs Temperature
2.0
1.6
1.2
0.8
O.4
0
V
T
=
1ꢀV
V
T
=
1ꢀV
S
A
V
= 15V
S
A
S
= 2ꢀ°C
= 2ꢀ°C
AT 10Hz
AT 1kHz
10nV
10nV
0
2
4
6
8
10
0
20
40
60
80
100
50
TEMPERATURE (°C)
125
–50
0
25
75 100
–25
TIME (SEC)
TIME (SEC)
1028 G07
1028 G08
1028 G09
1028fb
6
LT1028/LT1128
Typical perForMance characTerisTics
Distribution of Input Offset
Voltage
Offset Voltage Drift with Temperature
of Representative Units
Long-Term Stability of Five
Representative Units
20
18
16
14
12
10
8
50
40
10
8
V
T
=
15V
V
T
=
15V
V
= 15V
S
A
S
A
S
= 25°C
= 25°C
800 UNITS TESTED
FROM FOUR RUNS
t = 0 AFTER 1 DAY PRE-WARM UP
30
6
20
4
10
2
0
0
–10
–20
–30
–40
–50
–2
–4
–6
–8
–10
6
4
2
0
–50 –40 –30 –20 –10
0
10 20 30 40 50
–50
0
25
50
75 100 125
–25
0
1
3
4
5
2
OFFSET VOLTAGE (µV)
TEMPERATURE (°C)
TIME (MONTHS)
1028 G10
1028 G11
1028 G12
Input Bias and Offset Currents
Over Temperature
Bias Current Over the Common
Mode Range
Warm-Up Drift
60
50
40
30
24
20
100
80
V
V
=
CM
15V
= 0V
V
T
=
15V
S
S
A
20V
65nA
V
S
T
A
=
15V
R
CM
=
ª 300MΩ
= 25°C
= 25°C
60
POSITIVE INPUT CURRENT
(UNDERCANCELLED) DEVICE
40
16
12
METAL CAN (H) PACKAGE
20
0
BIAS CURRENT
20
10
0
8
4
0
–20
–40
–60
DUAL-IN-LINE PACKAGE
PLASTIC (N) OR CERDIP (J)
NEGATIVE INPUT CURRENT
(OVERCANCELLED) DEVICE
OFFSET CURRENT
–80
50
TEMPERATURE (°C)
100 125
–50 –25
0
25
75
0
1
2
3
4
5
–15
5
10
15
–10
–5
0
TIME AFTER POWER ON (MINUTES)
COMMON MODE INPUT VOLTAGE (V)
1028 G14
1028 G13
1028 G15
Output Short-Circuit Current
vs Time
Voltage Noise vs Supply Voltage
Supply Current vs Temperature
10
9
8
7
6
5
4
3
2
1
0
50
40
1.5
1.25
1.0
V
S
= 15V
T
= 25°C
A
–50°C
25°C
V
V
=
=
15V
5V
S
S
30
125°C
20
10
AT 10Hz
AT 1kHz
0
–10
–20
–30
–40
–50
125°C
25°C
0.75
0.5
–50°C
0
5
10
15
20
50
–50
0
25
75 100 125
0
2
3
–25
1
TEMPERATURE (°C)
TIME FROM OUTPUT SHORT TO GROUND (MINUTES)
SUPPLY VOLTAGE (V)
1028 G16
1028 G17
1028 G18
1028fb
7
LT1028/LT1128
Typical perForMance characTerisTics
LT1028
Gainꢁ Phase vs Frequency
LT1028
Capacitance Load Handling
Voltage Gain vs Frequency
70
60
50
40
30
20
70
60
50
40
30
20
160
140
120
100
80
80
70
60
50
40
30
20
10
0
30pF
V
= 1ꢀV
= 2ꢀ°C
= 2k
S
A
L
PHASE
T
2k
R
R
S
–
+
C
L
LT1128
LT1028
A
= –1, R = 2k
S
V
60
GAIN
A
S
= –10
V
40
R
= 200Ω
10
0
10
0
20
A
= –100
= 20Ω
V
R
V
T
= 15V
= 25°C
= 10pF
S
A
L
S
V
T
=
15V
0
S
A
C
= 25°C
–10
10k
–10
100M
–20
100k
1M
10M
10
100
1000
10000
0.01 0.1
1
10 100 1k 10k 100k 1M 10M 100M
FREQUENCY (Hz)
FREQUENCY (Hz)
CAPACITIVE LOAD (pF)
1028 G20
1028 G21
1028 G19
LT1128
Gain Phase vs Frequency
Gain Error vs Frequency
Closed-Loop Gain = 1000
LT1128
Capacitance Load Handling
1
0.1
70
60
50
40
30
20
70
60
50
40
30
20
80
70
60
50
40
30
20
10
0
30pF
TYPICAL
PRECISION
OP AMP
2k
PHASE
R
S
–
+
LT1128
C
L
A
V
= –1, R = 2k
S
V
LT1028
A
S
= –10
V
0.01
0.001
GAIN
R
= 200Ω
10
0
10
0
V
=
15V
= 25°C
= 10mV
S
A
O
V
T
= 15V
= 25°C
= 10pF
S
A
L
T
CLOSED-LOOP GAIN
OPEN-LOOP GAIN
GAIN ERROR =
1
V
P-P
C
A
= –100, R = 20Ω
S
–10
–10
100M
0.1
10
100
10k
100k
1M
10M
10
100
1000
10000
FREQUENCY (Hz)
FREQUENCY (Hz)
CAPACITIVE LOAD (pF)
1028 G22
1028 G23
1028 G24
Maximum Undistorted Output
vs Frequency
Voltage Gain vs Supply Voltage
Voltage Gain vs Load Resistance
100
10
1
30
25
20
15
10
5
100
10
1
V
=
15V
T
= 25°C
V
=
1ꢀV
S
A
L
A
S
T
= 25°C
= 2k
R
R
L
= 2k
T
= 2ꢀ°C
A
T
= –ꢀꢀ°C
A
T
= 12ꢀ°C
A
R
= 600Ω
L
LT1128
LT1028
I
= 3ꢀmA AT –ꢀꢀ°C
= 27mA AT 2ꢀ°C
= 16mA AT 12ꢀ°C
LMAX
10k
100k
1M
10M
0.1
1
10
0
5
10
20
15
FREQUENCY (Hz)
LOAD RESISTANCE (kΩ)
SUPPLY VOLTAGE (V)
1028 G26
1028 G27
1028 G25
1028fb
8
LT1028/LT1128
Typical perForMance characTerisTics
LT1028
Slew Rateꢁ Gain-Bandwidth
Product Over Temperature
LT1028
LT1028
Large-Signal Transient Response
Small-Signal Transient Response
18
17
16
15
90
80
70
60
V
= 15V
S
10V
50mV
GBW
FALL
RISE
5V/DIV
20mV/DIV
–10V
–50mV
14
13
12
50
40
30
1028 G28
1028 G29
1µs/DIV
0.2µs/DIV
A = –1, R = R = 2k,
C = 15pF, C = 80pF
A
= –1, R = R = 2k, C = 15pF
V
S
F
F
V S F
F
L
50
TEMPERATURE (°C)
100 125
–50 –25
0
25
75
1028 G30
LT1128
Slew Rateꢁ Gain-Bandwidth
Product Over Temperature
LT1128
LT1128
Large-Signal Transient Response
Small-Signal Transient Response
9
8
7
6
5
4
3
2
1
FALL
10V
0V
50mV
0V
RISE
GBW
30
20
10
–10V
–50mV
1028 G31
1028 G32
2µs/DIV
0.2µs/DIV
A
= –1, R = R = 2k, C = 30pF
A = –1, C = 10pF
V L
V
S
F
F
0
–50
50
75 100 125
–25
0
25
TEMPERATURE (°C)
1028 G33
LT1128
LT1028
Slew Rateꢁ Gain-Bandwidth Product
vs Over-Compensation Capacitor
Slew Rateꢁ Gain-Bandwidth Product
vs Over-Compensation Capacitor
Closed-Loop Output Impedance
100
10
1
1k
100
10
1
10k
100
10
I
= 1mA
O
S
A
V
=
1ꢀV
LT1128
T
= 2ꢀ°C
LT1028
SLEW
GBW
GBW
A
= 1000
100
10
1
1k
V
1
SLEW RATE
0.1
100
10
LT1128
A
= ꢀ
V
0.01
0.001
C
V
FROM PIN 5 TO PIN 6
OC
S
A
LT1028
=
15V
T
= 25°C
0.1
0.1
10
100
1k
10k
100k
1M
1
10
100
1000
10000
1
10
100
1000
10000
OVER-COMPENSATION CAPACITOR (pF)
FREQUENCY (Hz)
OVER-COMPENSATION CAPACITOR (pF)
1028 G35
1028 G36
1028 G34
1028fb
9
LT1028/LT1128
Typical perForMance characTerisTics
Power Supply Rejection Ratio
vs Frequency
Common Mode Limit Over
Temperature
Common Mode Rejection Ratio
vs Frequency
+
140
120
100
80
V
160
140
120
100
80
V
T
=
1ꢀV
S
A
V
=
1ꢀV
S
A
= 2ꢀ°C
–1
–2
–3
–4
T
= 2ꢀ°C
V
=
5V
S
=
V
15V
S
NEGATIVE
SUPPLY
LT1128
LT1028
POSITIVE
SUPPLY
60
4
3
2
1
60
40
V
=
5V TO 15V
40
S
20
20
–
0
V
0
100k
FREQUENCY (Hz)
10M
10
100
1k
10k
1M
100 1k
0.1
1
10
10k 100k 1M 10M
–50
0
25
50
75 100 125
–25
TEMPERATURE (°C)
FREQUENCY (Hz)
1028 G38
1028 G39
1028 G37
LT1028
Total Harmonic Distortion vs
Frequency and Load Resistance
LT1028
High Frequency Voltage Noise
vs Frequency
Total Harmonic Distortion vs
Closed-Loop Gain
0.1
0.01
0.1
10
1.0
0.1
V
= 20V
P-P
O
A
= 1000
L
V
f = 1kHz
R
= 2k
NON-INVERTING
GAIN
V
= 1ꢀV
= 2ꢀ°C
= 10k
S
A
A
L
= 1000
= 600Ω
T
V
R
R
L
0.01
A
= –1000
= 2k
V
L
R
INVERTING
GAIN
0.001
0.0001
A
= 1000
= 600Ω
V
L
R
V
V
= 20V
P-P
O
S
A
MEASURED
EXTRAPOLATED
=
1ꢀV
T
= 2ꢀ°C
0.001
1
10
100
10k
100k
1M
10
100
1k
10k 100k
FREQUENCY (kHz)
FREQUENCY (Hz)
CLOSED LOOP GAIN
1028 G40
1028 G41
1028 G42
LT1128
LT1128
Total Harmonic Distortion vs
Total Harmonic Distortion vs
Closed-Loop Gain
Frequency and Load Resistance
0.1
1.0
0.1
V
= 20V
P-P
O
NON-INVERTING
GAIN
f = 1kHz
V
= 1ꢀV
= 2ꢀ°C
= 10k
S
A
A
L
= 1000
= 600Ω
V
T
R
R
L
A
V
R
= 1000
L
0.01
0.001
= 2k
A
= –1000
= 2k
V
L
R
INVERTING
GAIN
A
= 1000
= 609Ω
V
L
0.01
R
V
V
T
= 20V
P-P
O
S
A
=
1ꢀV
MEASURED
EXTRAPOLATED
= 2ꢀ°C
0.001
0.0001
1.0
10
FREQUENCY (kHz)
100
10
100
1k
10k 100k
CLOSED LOOP GAIN
1028 G43
1028 G44
1028fb
10
LT1028/LT1128
applicaTions inForMaTion – noise
Voltage Noise vs Current Noise
the largest term, asin the example above, andthe LT1028/
LT1128’s voltage noise becomes negligible. As R is
eq
The LT1028/LT1128’s less than 1nV/√Hz voltage noise is
threetimesbetterthanthelowestvoltagenoiseheretofore
available(ontheLT1007/1037). Anecessaryconditionfor
suchlowvoltagenoiseisoperatingtheinputtransistorsat
nearly 1mA of collector currents, because voltage noise is
inversely proportional to the square root of the collector
current. Current noise, however, is directly proportional
to the square root of the collector current. Consequently,
the LT1028/LT1128’s current noise is significantly higher
than on most monolithic op amps.
further increased, current noise becomes important. At
1kHz, when R is in excess of 20k, the current noise
eq
component is larger than the resistor noise. The total
noise versus matched source resistance plot illustrates
the above calculations.
The plot also shows that current noise is more dominant
at low frequencies, such as 10Hz. This is because resistor
noise is flat with frequency, while the 1/f corner of current
noise is typically at 250Hz. At 10Hz when R > 1k, the
eq
current noise term will exceed the resistor noise.
Therefore, to realize truly low noise performance it is
important to understand the interaction between voltage
When the source resistance is unmatched, the total noise
versus unmatched source resistance plot should be con-
sulted. Note that total noise is lower at source resistances
below 1k because the resistor noise contribution is less.
noise (e ), current noise (I ) and resistor noise (r ).
n
n
n
Total Noise vs Source Resistance
The total input referred noise of an op amp is given by:
When R > 1k total noise is not improved, however. This
S
is because bias current cancellation is used to reduce
input bias current. The cancellation circuitry injects two
correlated current noise components into the two inputs.
With matched source resistors the injected current noise
creates a common-mode voltage noise and gets rejected
by the amplifier. With source resistance in one input only,
the cancellation noise is added to the amplifier’s inherent
noise.
2
2
2 1/2
e = [e + r + (I R ) ]
t
n
n
n eq
where R is the total equivalent source resistance at the
eq
two inputs, and
r = √4kTR = 0.13√Req in nV/√Hz at 25°C
n
eq
As a numerical example, consider the total noise at 1kHz
of the gain 1000 amplifier shown in Figure 1.
100Ω
100k
In summary, the LT1028/LT1128 are the optimum am-
plifiers for noise performance, provided that the source
resistanceiskeptlow.Thefollowingtabledepictswhichop
amp manufactured by Linear Technology should be used
to minimize noise, as the source resistance is increased
beyond the LT1028/LT1128’s level of usefulness.
–
LT1028
LT1128
+
100Ω
1028 F01
Table 1. Best Op Amp for Lowest Total Noise vs Source Resistance
Figure 1
BEST OP AMP
SOURCE RESIS-
TANCE (Ω) (Note 1) AT LOW FREQ (10Hz)
WIDEBAND (1kHz)
LT1028/LT1128
LT1028/LT1128
LT1007/LT1037
LT1001
R
= 100Ω + 100Ω || 100k ≈ 200Ω
r = 0.13√200 = 1.84nV√Hz
eq
0 to 400
400 to 4k
4k to 40k
40k to 500k
500k to 5M
>5M
LT1028/LT1128
LT1007/1037
LT1001
n
n
e = 0.85nV√Hz
I = 1.0pA/√Hz
n
LT1012
2
2
2 1/2
e = [0.85 + 1.84 + (1.0 × 0.2) ] = 2.04nV/√Hz
t
LT1012 or LT1055
LT1055
LT1012
LT1055
Output noise = 1000 e = 2.04µV/√Hz
t
Note 1: Source resistance is defined as matched or unmatched, e.g.,
R = 1k means: 1k at each input, or 1k at one input and zero at the other.
At very low source resistance (R < 40Ω) voltage noise
dominates. As R is increased resistor noise becomes
eq
S
eq
1028fb
11
LT1028/LT1128
applicaTions inForMaTion – noise
Noise Testing – Voltage Noise
Measuring the typical 35nV peak-to-peak noise per-
formance of the LT1028/LT1128 requires special test
precautions:
The LT1028/LT1128’s RMS voltage noise density can be
accurately measured using the Quan Tech Noise Analyzer,
Model 5173 or an equivalent noise tester. Care should be
taken,however,tosubtractthenoiseofthesourceresistor
used. Prefabricated test cards for the Model 5173 set the
device under test in a closed-loop gain of 31 with a 60Ω
source resistor and a 1.8k feedback resistor. The noise
of this resistor combination is 0.13√58 = 1.0nV/√Hz. An
(a) The device should be warmed up for at least five
minutes. As the op amp warms up, its offset voltage
changes typically 10µV due to its chip temperature
increasing 30°C to 40°C from the moment the power
suppliesareturnedon. Inthe10secondmeasurement
interval these temperature-induced effects can easily
exceed tens of nanovolts.
2
LT1028/LT1128 with 0.85nV/√Hz noise will read (0.85 +
2 1/2
1.0 ) = 1.31nV/√Hz. For better resolution, the resistors
(b) For similar reasons, the device must be well shielded
from air current to eliminate the possibility of ther-
moelectric effects in excess of a few nanovolts, which
would invalidate the measurements.
should be replaced with a 10Ω source and 300Ω feedback
resistor. Even a 10Ω resistor will show an apparent noise
which is 8% to 10% too high.
The 0.1Hz to 10Hz peak-to-peak noise of the LT1028/
LT1128 is measured in the test circuit shown. The fre-
quency response of this noise tester indicates that the
0.1Hz corner is defined by only one zero. The test time
to measure 0.1Hz to 10Hz noise should not exceed 10
seconds, as this time limit acts as an additional zero to
eliminate noise contributions from the frequency band
below 0.1Hz.
(c) Sudden motion in the vicinity of the device can also
feedthrough to increase the observed noise.
Anoise-voltagedensitytestisrecommendedwhenmeasur-
ing noise on a large number of units. A 10Hz noise-voltage
density measurement will correlate well with a 0.1Hz to
10Hz peak-to-peak noise reading since both results are
determined by the white noise and the location of the 1/f
corner frequency.
0.1µF
100k
100
90
80
–
2k
70
22µF
+
10Ω
*
SCOPE
4.3k
× 1
+
LT1001
60
4.7µF
R
IN
= 1M
–
2.2µF
110k
50
40
30
100k
VOLTAGE GAIN = 50,000
* DEVICE UNDER TEST
0.1µF
24.3k
0.01
0.1
1.0
10
100
NOTE ALL CAPACITOR VALUES ARE FOR
NONPOLARIZED CAPACITORS ONLY
1028 F02
FREQUENCY (Hz)
1028 F03
Figure 2. 0.1Hz to 10Hz Noise Test Circuit
Figure 3. 0.1Hz to 10Hz Peak-to-Peak
Noise Tester Frequency Response
1028fb
12
LT1028/LT1128
applicaTions inForMaTion – noise
Noise Testing – Current Noise
10Hz voltage noise density is sample tested on every lot.
Devices 100% tested at 10Hz are available on request for
an additional charge.
Current noise density (I ) is defined by the following for-
n
mula,andcanbemeasuredinthecircuitshowninFigure4.
10Hz current noise is not tested on every lot but it can be
inferred from 100% testing at 1kHz. A look at the current
noise spectrum plot will substantiate this statement. The
only way 10Hz current noise can exceed the guaranteed
limits is if its 1/f corner is higher than 800Hz and/or its
white noise is high. If that is the case then the 1kHz test
will fail.
1/2
2
)
⎡
⎢
⎣
⎤
⎥
⎦
eno2 − 31•18.4nV/ Hz
(
ln =
20k • 31
1.8k
10k
–
LT1028
60Ω
e
no
LT1128
+
10k
10
0
1028 F04
Figure 4
–10
–20
If the Quan Tech Model 5173 is used, the noise reading is
input-referred, therefore the result should not be divided
by 31; the resistor noise should not be multiplied by 31.
CURRENT
NOISE
VOLTAGE
NOISE
–30
–40
–50
100% Noise Testing
100
1k
10k
100k
The 1kHz voltage and current noise is 100% tested on
the LT1028/LT1128 as part of automated testing; the
approximate frequency response of the filters is shown.
The limits on the automated testing are established by
extensive correlation tests on units measured with the
Quan Tech Model 5173.
FREQUENCY (Hz)
1028 F05
Figure ꢀ. Automated Tester Noise Filter
1028fb
13
LT1028/LT1128
applicaTions inForMaTion
General
10k*
15V
7
TheLT1028/LT1128seriesdevicesmaybeinserteddirectly
into OP-07, OP-27, OP-37, LT1007 and LT1037 sockets
withorwithoutremovalofexternalnullingcomponents.In
addition,theLT1028/LT1128maybefittedto5534sockets
with the removal of external compensation components.
2
3
–
6
LT1028
LT1128
V
200Ω*
10k*
O
+
4
–15V
V
= 100V
O
OS
* RESISTORS MUST HAVE LOW
THERMOELECTRIC POTENTIAL
Offset Voltage Adjustment
1028 F07
TheinputoffsetvoltageoftheLT1028/LT1128anditsdrift
with temperature, are permanently trimmed at wafer test-
Figure 7. Test Circuit for Offset Voltage
and Offset Voltage Drift with Temperature
ing to a low level. However, if further adjustment of V is
OS
necessary, the use of a 1k nulling potentiometer will not
degrade drift with temperature. Trimming to a value other
Unity-Gain Buffer Applications (LT1128 Only)
When R ≤ 100Ω and the input is driven with a fast, large-
F
than zero creates a drift of (V /300)µV/°C, e.g., if V
OS
OS
signalpulse(>1V),theoutputwaveformwilllookasshown
is adjusted to 300µV, the change in drift will be 1µV/°C.
in the pulsed operation diagram (Figure 8).
The adjustment range with a 1k pot is approximately
1.1mV.
R
F
1k
–
15V
1
OUTPUT
6V/µs
2
3
8
–
7
+
6
LT1028
LT1128
1028 F08
INPUT
OUTPUT
+
4
Figure 8
1028 F06
–15V
During the fast feedthrough-like portion of the output, the
input protection diodes effectively short the output to the
inputandacurrent, limitedonlybytheoutputshort-circuit
protection, will be drawn by the signal generator. With
Figure 6
Offset Voltage and Drift
Thermocouple effects, caused by temperature gradients
across dissimilar metals at the contacts to the input termi-
nals, can exceed the inherent drift of the amplifier unless
proper care is exercised. Air currents should be minimized,
package leads should be short, the two input leads should
be close together and maintained at the same temperature.
R
≥ 500Ω, the output is capable of handling the current
F
requirements (I ≤ 20mA at 10V) and the amplifier stays
L
in its active mode and a smooth transition will occur.
As with all operational amplifiers when R > 2k, a pole will
F
be created with RF and the amplifier’s input capacitance,
creating additional phase shift and reducing the phase
margin. A small capacitor (20pF to 50pF) in parallel with
The circuit shown in Figure 7 to measure offset voltage
is also used as the burn-in configuration for the LT1028/
LT1128.
R will eliminate this problem.
F
1028fb
14
LT1028/LT1128
applicaTions inForMaTion
Frequency Response
C1
TheLT1028’sGain, PhasevsFrequencyplotindicatesthat
the device is stable in closed-loop gains greater than +2 or
–1becausephasemarginisabout50°atanopen-loopgain
of6dB. Inthevoltagefollowerconfigurationphasemargin
seems inadequate. This is indeed true when the output is
shorted to the inverting input and the noninverting input
is driven from a 50Ω source impedance. However, when
R1
R
S1
–
LT1028
R
S2
+
1028 F10
Figure 10
feedback is through a parallel R-C network (provided C
F
< 68pF), the LT1028 will be stable because of interaction
between the input resistance and capacitance and the
feedback network. Larger source resistance at the non-
inverting input has a similar effect. The following voltage
follower configurations are stable:
If C is only used to cut noise bandwidth, a similar effect
F
can be achieved using the over-compensation terminal.
The Gain, Phase plot also shows that phase margin is
about45°atgainof10(20dB).Thefollowingconfiguration
has a high (≈70%) overshoot without the 10pF capacitor
because of additional phase shift caused by the feedback
resistor–inputcapacitancepole.Thepresenceofthe10pF
capacitor cancels this pole and reduces overshoot to 5%.
33pF
2k
–
+
–
+
10pF
LT1028
LT1028
500Ω
50Ω
10k
1.1k
50Ω
–
LT1028
1028 F09
+
Figure 9
50Ω
Another configuration which requires unity-gain stability
1028 F11
is shown below. When C is large enough to effectively
F
short the output to the input at 15MHz, oscillations can
Figure 11
occur.TheinsertionofR ≥500ΩwillpreventtheLT1028
S2
Over-Compensation
from oscillating. When R ≥ 500Ω, the additional noise
S1
contribution due to the presence of R will be minimal.
The LT1028/LT1128 are equipped with a frequency over-
compensation terminal (Pin 5). A capacitor connected
between Pin 5 and the output will reduce noise bandwidth.
DetailsareshownontheSlewRate,Gain-BandwidthProd-
uct vs Over-Compensation Capacitor plot. An additional
benefit is increased capacitive load handling capability.
S2
When R ≤ 100Ω, R is not necessary, because R
S1
S2
S1
F
represents a heavy load on the output through the C
short. When 100Ω < R < 500Ω, R should match R .
S1
S2
S1
For example, R = R = 300Ω will be stable. The noise
S1
S2
increase due to R is 40%.
S2
1028fb
15
LT1028/LT1128
Typical applicaTions
Strain Gauge Signal Conditioner with Bridge Excitation
15V
7
330Ω
3
5.0V
+
–
LT1021-5
6
LT1128
2
4
–15V
REFERENCE
OUTPUT
15V
7
350Ω
BRIDGE
3
–
6
0V TO 10V
OUTPUT
LT1028
301k*
10k
ZERO
TRIM
2
+
1µF
4
30.1k*
–15V
15V
7
5k
GAIN
TRIM
3
2
–
49.9Ω*
*RN60C FILM RESISTORS
6
LT1028
+
330Ω
4
THE LT1028’s NOISE CONTRIBUTION IS NEGLIGIBLE
COMPARED TO THE BRIDGE NOISE.
–15V
1028 TA03
Low Noise Voltage Regulator
28V
10
+
121Ω
2.3k
LT317A
10
PROVIDES PRE-REG
AND CURRENT
LIMITING
28V
1k
+
–
LT1021-10
330Ω
LT1028
2N6387
1000pF
20V OUTPUT
2k
2k
1028 TA04
1028fb
16
LT1028/LT1128
Typical applicaTions
Paralleling Amplifiers to Reduce Voltage Noise
+
1.5k
A1
LT1028
–
7.5Ω
470Ω
4.7k
+
1.5k
1.5k
A2
LT1028
–
+
OUTPUT
LT1028
–
7.5Ω
470Ω
+
An
LT1028
–
7.5Ω
470Ω
1. ASSUME VOLTAGE NOISE OF LT1028 AND 7.5Ω SOURCE RESISTOR = 0.9nV/√Hz.
2. GAIN WITH n LT1028s IN PARALLEL = n • 200.
3. OUTPUT NOISE = √n • 200 • 0.9nV/√Hz.
0.9
√n
OUTPUT NOISE
4. INPUT REFERRED NOISE =
=
nV/√Hz.
n • 200
5. NOISE CURRENT AT INPUT INCREASES √n TIMES.
2µV
√5
6. IF n = 5, GAIN = 1000, BANDWIDTH = 1MHz, RMS NOISE, DC TO 1MHz =
= 0.9µV.
1028 TA05
1028fb
17
LT1028/LT1128
Typical applicaTions
Phono Preamplifier
10Ω
787Ω
15V
0.1µF
10k
2
3
7
0.33µF
–
+
6
OUTPUT
100pF
47k
LT1028
4
–15V
ALL RESISTORS METAL FILM
MAG PHONO
INPUT
1028 TA06
Tape Head Amplifier
0.1µF
499Ω
31.6k
10Ω
2
–
6
OUTPUT
LT1028
3
TAPE HEAD
INPUT
+
1028 TA07
ALL RESISTORS METAL FILM
1028fb
18
LT1028/LT1128
Typical applicaTions
Low Noiseꢁ Wide Bandwidth Instrumentation Amplifier
–INPUT
+
300Ω
10k
LT1028
–
820Ω
68pF
50Ω
10Ω
–
+
68pF
300Ω
820Ω
OUTPUT
LT1028
–
+
LT1028
+INPUT
10k
GAIN = 1000, BANDWIDTH = 1MHz
INPUT REFERRED NOISE = 1.5nV/√Hz AT 1kHz
WIDEBAND NOISE –DC to 1MHz = 3µV
RMS
IF BW LIMITED TO DC TO 100kHz = 0.55µV
1028 TA08
RMS
Gyro Pick-Off Amplifier
GYRO TYPICAL–
NORTHROP CORP.
GR-F5AH7-5B
SINE
DRIVE
+
OUTPUT TO SYNC
DEMODULATOR
LT1028
•
–
1k
100Ω
1028 TA09
1028fb
19
LT1028/LT1128
Typical applicaTions
Super Low Distortion Variable Sine Wave Oscillator
R1
C2
C1
0.047
0.047
20Ω
2k
1V
OUTPUT
20Ω
RMS
+
1.5kHz TO 15kHz
2k
1
f =
LT1028
(
)
2πRC
R2
–
WHERE R1C1 = R2C2
4.7k
15V
5.6k
2.4k
LT1004-1.2V
10pF
22k
15µF
MOUNT 1N4148s
IN CLOSE PROXIMITY
–
+
10k
2N4338
100k
LT1055
560Ω
TRIM FOR
LOWEST
DISTORTION
20k
10k
<0.0018% DISTORTION AND NOISE.
MEASUREMENT LIMITED BY RESOLUTION OF
HP339A DISTORTION ANALYZER
1028 TA10
Chopper-Stabilized Amplifier
15V
1N758
3
2
7
+
6
LT1052
8
–
4
1
0.1
0.1
0.01
1N758
15V
–15V
130Ω
3
68Ω
30k
100k
1
7
INPUT
+
8
LT1028
OUTPUT
10k
2
–
4
–15V
10Ω
1028 TA11
1028fb
20
LT1028/LT1128
scheMaTic DiagraM
NULL
8
+
V
7
R5
130Ω
R6
130Ω
NULL
1
Q4
1.1mA
2.3mA
400µA
R2
3k
R1
3k
C1
257pF
500µA
R10
400Ω
R11
400Ω
Q17
Q16
Q19
Q18
R10
500Ω
900µA
900µA
C2
Q26
Q6
Q5
1
3
3
1
Q11
R11
100Ω
Q22
NON-
INVERTING
INPUT
Q9
Q8
Q7
C3
250pF
4.5µA
3
Q10
4.5µA
OUTPUT
6
Q24
4.5µA
4.5µA
Q25
Q2
Q1
1.5µA
Q12
C4
35pF
R12
240Ω
Q13
Q14
Q27
1.5µA
INVERTING
INPUT
0
2
1.8mA
300µA
Q3
Q15
Q23
BIAS
Q21
R8
480Ω
600µA
R7
80Ω
Q20
–
V
4
1028 TA12
OVER-COMP
5
C2 = 50pF for LT1028
C2 = 275pF for LT1128
1028fb
21
LT1028/LT1128
package DescripTion
Please refer to http://www.linear.com/designtools/packaging/ for the most recent package drawings.
J8 Package
3-Lead CERDIP (Narrow .300 Inch, Hermetic)
(Reference LTC DWG # 05-08-1110)
.405
(10.287)
MAX
CORNER LEADS OPTION
(4 PLCS)
.005
(0.127)
MIN
6
5
4
8
7
2
.023 – .045
(0.584 – 1.143)
HALF LEAD
OPTION
.025
(0.635)
RAD TYP
.220 – .310
(5.588 – 7.874)
.045 – .068
(1.143 – 1.650)
FULL LEAD
OPTION
1
3
.200
.300 BSC
(5.080)
MAX
(7.62 BSC)
.015 – .060
(0.381 – 1.524)
.008 – .018
(0.203 – 0.457)
0° – 15°
.045 – .065
(1.143 – 1.651)
.125
3.175
MIN
NOTE: LEAD DIMENSIONS APPLY TO SOLDER DIP/PLATE
OR TIN PLATE LEADS
.014 – .026
(0.360 – 0.660)
.100
(2.54)
BSC
J8 0801
OBSOLETE PACKAGE
1028fb
22
LT1028/LT1128
package DescripTion
Please refer to http://www.linear.com/designtools/packaging/ for the most recent package drawings.
N Package
8-Lead PDIP (Narrow .300 Inch)
(Reference LTC DWG # 05-08-1510 Rev I)
.400*
(10.160)
MAX
8
7
6
5
4
.255 ±.015*
(6.477 ±0.381)
1
2
3
.130 ±.005
.300 – .325
.045 – .065
(3.302 ±0.127)
(1.143 – 1.651)
(7.620 – 8.255)
.065
(1.651)
TYP
.008 – .015
(0.203 – 0.381)
.120
.020
(0.508)
MIN
(3.048)
MIN
+.035
.325
–.015
.018 ±.003
(0.457 ±0.076)
.100
(2.54)
BSC
+0.889
8.255
N8 REV I 0711
(
)
–0.381
NOTE:
INCHES
1. DIMENSIONS ARE
MILLIMETERS
*THESE DIMENSIONS DO NOT INCLUDE MOLD FLASH OR PROTRUSIONS.
MOLD FLASH OR PROTRUSIONS SHALL NOT EXCEED .010 INCH (0.254mm)
1028fb
23
LT1028/LT1128
package DescripTion
Please refer to http://www.linear.com/designtools/packaging/ for the most recent package drawings.
S8 Package
8-Lead Plastic Small Outline (Narrow .150 Inch)
(Reference LTC DWG # 05-08-1610 Rev G)
.189 – .197
(4.801 – 5.004)
.045 ±.005
NOTE 3
.050 BSC
7
5
8
6
.245
MIN
.160 ±.005
.150 – .157
(3.810 – 3.988)
NOTE 3
.228 – .244
(5.791 – 6.197)
.030 ±.005
TYP
1
3
4
2
RECOMMENDED SOLDER PAD LAYOUT
.010 – .020
(0.254 – 0.508)
× 45°
.053 – .069
(1.346 – 1.752)
.004 – .010
(0.101 – 0.254)
.008 – .010
(0.203 – 0.254)
0°– 8° TYP
.016 – .050
(0.406 – 1.270)
.050
(1.270)
BSC
.014 – .019
(0.355 – 0.483)
TYP
NOTE:
INCHES
1. DIMENSIONS IN
(MILLIMETERS)
2. DRAWING NOT TO SCALE
3. THESE DIMENSIONS DO NOT INCLUDE MOLD FLASH OR PROTRUSIONS.
MOLD FLASH OR PROTRUSIONS SHALL NOT EXCEED .006" (0.15mm)
4. PIN 1 CAN BE BEVEL EDGE OR A DIMPLE
SO8 REV G 0212
1028fb
24
LT1028/LT1128
package DescripTion
Please refer to http://www.linear.com/designtools/packaging/ for the most recent package drawings.
S Package
16-Lead Plastic Small Outline (Narrow .150 Inch)
(Reference LTC DWG # 05-08-1610 Rev G)
.386 – .394
(9.804 – 10.008)
.045 .005
NOTE 3
.050 BSC
16
N
15
14
13
12
11
10
9
N
1
.245
MIN
.160 .005
.150 – .157
(3.810 – 3.988)
NOTE 3
.228 – .244
(5.791 – 6.197)
2
3
N/2
N/2
8
.030 .005
TYP
RECOMMENDED SOLDER PAD LAYOUT
2
3
5
6
7
1
4
.010 – .020
(0.254 – 0.508)
× 45°
.053 – .069
(1.346 – 1.752)
.004 – .010
(0.101 – 0.254)
.008 – .010
(0.203 – 0.254)
0° – 8° TYP
.050
(1.270)
BSC
.014 – .019
(0.355 – 0.483)
TYP
.016 – .050
(0.406 – 1.270)
S16 REV G 0212
NOTE:
1. DIMENSIONS IN
INCHES
(MILLIMETERS)
2. DRAWING NOT TO SCALE
3. THESE DIMENSIONS DO NOT INCLUDE MOLD FLASH OR PROTRUSIONS.
MOLD FLASH OR PROTRUSIONS SHALL NOT EXCEED .006" (0.15mm)
4. PIN 1 CAN BE BEVEL EDGE OR A DIMPLE
1028fb
25
LT1028/LT1128
package DescripTion
Please refer to http://www.linear.com/designtools/packaging/ for the most recent package drawings.
H Package
8-Lead TO-5 Metal Can (.230 Inch PCD)
(Reference LTC DWG # 05-08-1321)
.335 – .370
(8.509 – 9.398)
DIA
.305 – .335
(7.747 – 8.509)
.040
(1.016)
MAX
.050
(1.270)
MAX
.165 – .185
(4.191 – 4.699)
REFERENCE
PLANE
SEATING
PLANE
GAUGE
PLANE
.500 – .750
(12.700 – 19.050)
.010 – .045*
(0.254 – 1.143)
.016 – .021**
(0.406 – 0.533)
.027 – .045
(0.686 – 1.143)
45°
PIN 1
.028 – .034
(0.711 – 0.864)
.230
(5.842)
TYP
.110 – .160
(2.794 – 4.064)
INSULATING
STANDOFF
*LEAD DIAMETER IS UNCONTROLLED BETWEEN THE REFERENCE PLANE
AND THE SEATING PLANE
.016 – .024
(0.406 – 0.610)
**FOR SOLDER DIP LEAD FINISH, LEAD DIAMETER IS
H8 (TO-5) 0.230 PCD 0204
OBSOLETE PACKAGE
1028fb
26
LT1028/LT1128
revision hisTory (Revision history begins at Rev B)
REV
DATE
DESCRIPTION
PAGE NUMBER
B
10/12 Replaced the Typical Application.
1
1028fb
Information furnished by Linear Technology Corporation is believed to be accurate and reliable.
However, no responsibility is assumed for its use. Linear Technology Corporation makes no representa-
tion that the interconnection of its circuits as described herein will not infringe on existing patent rights.
27
LT1028/LT1128
Typical applicaTion
Low Noise Infrared Detector
5V
10Ω
+
100µF
1k
33Ω
SYNCHRONOUS
DEMODULATOR
+
100µF
10k*
10k*
OPTICAL
CHOPPER
WHEEL
267Ω
5V
7
5V
1000µF
2
3
2
7
5V
+
+
IR
1/4 LTC1043
6
2
3
7
6
LM301A
RADIATION
+
13
LT1028
39Ω
8
3
6
8
12
16
–
1M
DC OUT
LT1012
PHOTO-
ELECTRIC
PICK-OFF
–
1
4
10k
8
4
–
1
–5V
14
–5V
30pF
4
INFRA RED ASSOCIATES, INC.
HgCdTe IR DETECTOR
13Ω AT 77°K
–5V
10Ω
1028 TA13
relaTeD parTs
PART NUMBER
DESCRIPTION
325MHz, 3.5nV/√Hz Single and Dual Op Amps
COMMENTS
Slew Rate = 140V/µs, Low Distortion at 5MHz: –80dBc
LT1806/LT1807
1028fb
LT 1012 REV B • PRINTED IN USA
LinearTechnology Corporation
1630 McCarthy Blvd., Milpitas, CA 95035-7417
28
●
●
LINEAR TECHNOLOGY CORPORATION 1992
(408) 432-1900 FAX: (408) 434-0507 www.linear.com
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