LT1204CN#PBF [Linear]
LT1204 - 4-Input Video Multiplexer with 75MHz Current Feedback Amplifier; Package: PDIP; Pins: 16; Temperature Range: 0°C to 70°C;
| 型号： | LT1204CN#PBF |
| 厂家： | 
Linear |
| 描述： | LT1204 - 4-Input Video Multiplexer with 75MHz Current Feedback Amplifier; Package: PDIP; Pins: 16; Temperature Range: 0°C to 70°C 复用器 放大器 |
| 文件： | 总20页 (文件大小：333K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
LT1204
4-Inp ut Vid e o Multip le xe r
with 75MHz Curre nt
Fe e d b a c k Am p lifie r
U
DESCRIPTIO
EATURE
S
F
The LT®1204 is a 4-input video multiplexer designed to
drive 75Ω cables and easily expand into larger routing
systems. Wide bandwidth, high slew rate, and low differ-
ential gain and phase make the LT1204 ideal for broadcast
quality signal routing. Channel separation and disable
isolation are greater than 90dB up to 10MHz. The channel-
■
■
■
■
■
■
■
■
■
■
■
■
0.1dB Gain Flatness > 30MHz
Channel Separation at 10MHz: 90dB
40mV Switching Transient, Input Referred
–3dB Bandwidth, AV = 2, RL = 150Ω: 75MHz
Channel-to-Channel Switching Time: 120ns
Easy to Expand for More Inputs
Large Input Range: ± 6V
to-channel output switching transient is only 40mV ,
P-P
0.04% Differential Gain, RL = 150Ω
0.06° Differential Phase, RL = 150Ω
High Slew Rate: 1000V/µs
Output Swing, RL = 400Ω: ±13V
Wide Supply Range: ±5V to ±15V
with a 50ns duration, making the transition imperceptible
on high quality monitors.
A unique feature of the LT1204 is its ability to expand into
larger routing matrices. This is accomplished by a patent
pending circuit that bootstraps the feedback resistors in
thedisablecondition, raisingthetrueoutputimpedanceof
the circuit. The effect of this feature is to eliminate cable
misterminations in large systems.
O U
PPLICATI
S
A
■
Broadcast Quality Video Multiplexing
Large Matrix Routing
Medical Imaging
Large Amplitude Signal Multiplexing
Programmable Gain Amplifiers
■
■
■
■
The large input and output signal levels supported by the
LT1204 when operated on ±15V supplies make it ideal for
general purpose analog signal selection and multiplexing.
A shutdown feature reduces the supply current to 1.5mA.
, LTC and LT are registered trademarks of Linear Technology Corporation.
U
O
TYPICAL APPLICATI
All Hostile Crosstalk
Surface Mount PCB Measurements
V
IN0
1
16
+
V
IN0
+1
15V
V
+
–
75Ω
75Ω
75Ω
75Ω
75Ω
V
2
3
15
14
O
–20
–40
V
OUT
CFA
GND
V = ±15V
S
V
IN 0
= GND
V
IN1
–
V
R
F
1k
IN1
+1
V
–15V
V
R
= 0dBm
= 100Ω
IN 1,2,3
L
R
G
1k
4
5
FB 13
GND
–60
V
IN2
S/D 12
ENABLE 11
A1 10
V
IN2
+1
–80
6
7
GND
LOGIC
–100
–120
V
IN3
V
IN3
A0
9
+1
1
10
100
8
REF
LT1204
FREQUENCY (MHz)
1204 TA01
1204 TA02
–15V
6.8k
8.2k
1
LT1204
W W W
U
ABSOLUTE AXI U RATI GS
Operating Temperature Range ............... –40°C to 85°C
Storage Temperature Range ................ –65°C to 150°C
Junction Temperature (Note 4)............................ 150°C
Lead Temperature (Soldering, 10 sec).................. 300°C
Supply Voltage ..................................................... ±18V
– Input Current (Pin 13) .................................... ±15mA
+Input and Control/Logic Current (Note 1) ........ ±50mA
Output Short-Circuit Duration (Note 2).........Continuous
Specified Temperature Range (Note 3)....... 0°C to 70°C
W
U
/O
PACKAGE RDER I FOR ATIO
TOP VIEW
TOP VIEW
ORDER PART
ORDER PART
+
NUMBER
+
V
1
2
3
4
5
6
7
8
16
15
14
V
NUMBER
IN0
1
2
3
4
5
6
7
8
V
16
15
14
13
12
11
10
9
V
IN0
GND
V
O
V
O
GND
–
–
V
IN1
V
LT1204CN*
V
LT1204CSW*
V
IN1
GND
13 FB
FB
GND
V
IN2
12 SHDN
11 ENABLE
10 A1
SHDN
ENABLE
A1
V
IN2
GND
GND
V
IN3
V
IN3
REF
9
A0
A0
REF
SW PACKAGE
16-LEAD PLASTIC SO
N PACKAGE
16-LEAD PDIP
*See Note 3
*See Note 3
TJMAX = 150°C, θJA = 70°C/W
TJMAX = 150°C, θJA = 90°C/W
Consult factory for Industrial and Military grade parts.
ELECTRICAL CHARACTERISTICS
0°C ≤ TA ≤ 70°C, ±5V ≤ V ≤ ±15V, VCM = 0V, Pin 8 grounded and pulse tested unless otherwise noted.
S
SYMBOL
PARAMETER
CONDITIONS
Any Positive Input, T = 25°C
MIN
TYP
MAX
UNITS
V
OS
Input Offset Voltage
5
14
16
mV
mV
A
●
●
●
Offset Matching
Between Any Positive Input, V = ±15V
0.5
40
3
5
mV
S
Input Offset Voltage Drift
Positive Input Bias Current
Any Positive Input
µV/°C
+
I
Any Positive Input, T = 25°C
8
10
µA
µA
IN
A
●
●
–
I
Negative Input Bias Current
T = 25°C
A
±20
±100
±150
µA
µA
IN
e
Input Noise Voltage
f = 1kHz, R = 1k, R = 10Ω, R = 0Ω
7
nV/√Hz
pA/√Hz
pA/√Hz
n
F
G
S
+i
Noninverting Input Noise Current Density
Inverting Input Noise Current Density
Input Capacitance
f = 1kHz
f = 1kHz
1.5
40
n
–i
n
C
Input Selected
Input Deselected
3.0
3.5
pF
pF
IN
C
Output Capacitance
Disabled, Pin 11 Voltage = 0V
V = ±5V, V = –1.5V, 2V, T = 25°C
8
pF
OUT
R
IN
Positive Input Resistance, Any Positive Input
5
4
20
20
MΩ
MΩ
S
IN
A
V = ±15V, V = ±5V
●
S
IN
2
LT1204
ELECTRICAL CHARACTERISTICS
0°C ≤ TA ≤ 70°C, ±5V ≤ V ≤ ±15V, VCM = 0V, Pin 8 grounded and pulse tested unless otherwise noted.
S
SYMBOL
PARAMETER
CONDITIONS
V = ±5V, T = 25°C
MIN
TYP
MAX
UNITS
Input Voltage Range, Any Positive Input
2.0
–1.5
±5.0
3.75
2.5
–2.0
±6.0
4.0
V
V
V
V
S
A
V = ±15V
●
●
S
V = ±15V, Pin 8 Voltage = –5V
S
CMRR
PSRR
Common Mode Rejection Ratio
V = ±5V, V = –1.5V, 2V, T = 25°C
48
48
55
58
dB
dB
S
CM
A
V = ±15V, V = ±5V
●
S
CM
Negative Input Current
Common Mode Rejection
V = ±5V, V = –1.5V, 2V, T = 25°C
0.05
0.05
1
1
µA/V
µA/V
S
CM
A
V = ±15V, V = ±5V
●
●
●
S
CM
Power Supply Rejection Ratio
V = ±4.5V to ±15V
S
60
76
dB
Negative Input Current Power Supply Rejection V = ±4.5V to ±15V
0.5
5
µA/V
S
A
VOL
Large-Signal Voltage Gain
V = ±15V, V = ±10V, R = 1k
●
●
57
57
73
66
dB
dB
S
OUT
L
V = ±5V, V = ±2V, R = 150Ω
S
OUT
L
R
OL
Transresistance
V = ±15V, V = ±10V, R = 1k
V = ±5V, V = ±2V, R = 150Ω
S OUT L
●
●
115
115
310
210
kΩ
kΩ
S
OUT
L
–
∆V /∆I
O
IN
V
Output Voltage Swing
V = ±15V, R = 400Ω, T = 25°C
±12
±10
±13.5
±3.7
55
V
V
OUT
S
L
A
●
●
V = ±5V, R = 150Ω, T = 25°C
±3.0
±2.5
V
V
S
L
A
I
Output Current
R = 0Ω, T = 25°C
35
125
mA
OUT
L
A
I
S
Supply Current (Note 5)
Pin 11 = 5V
Pin 11 = 0V
Pin 12 = 0V
●
●
●
19
19
1.5
24
24
3.5
mA
mA
mA
Disabled Output Resistance
V = ±15V, Pin 11 = 0V, V = ±5V,
S O
R = R = 1k
●
●
14
8
25
20
kΩ
kΩ
F
G
V = ±15V, Pin 11 = 0V, V = ±5V,
S
O
R = 2k, R = 222Ω
F
G
U
DIGITAL I PUT CHARACTERISTICS
0°C ≤ TA ≤ 70°C, V = ±15V, RF = 2k, RG = 220Ω, RL = 400Ω unless otherwise noted.
S
SYMBOL
PARAMETER
CONDITIONS
MIN
TYP
MAX
UNITS
V
V
IL
Input Low Voltage
Pins 9, 10, 11, 12
●
●
●
●
●
●
●
0.8
V
IH
Input High Voltage
Pins 9, 10, 11, 12
2
V
I
IL
Input Low Current
Pins 9, 10 Voltage = 0V
Pins 9, 10 Voltage = 5V
Pin 11 Voltage = 0V
Pin 11 Voltage = 5V
1.5
10
6
µA
nA
µA
µA
µA
ns
I
IH
Input High Current
150
15
Enable Low Input Current
Enable High Input Current
Shutdown Input Current
Channel-to-Channel Select Time (Note 6)
Disable Time (Note 7)
4.5
200
20
300
80
I
Pin 12 Voltage 0V ≤ V
≤ 5V
SHDN
SHDN
t
t
t
t
Pin 8 Voltage = –5V, T = 25°C
120
40
240
100
200
10
sel
A
Pin 8 Voltage = –5V, T = 25°C
ns
dis
A
Enable Time (Note 8)
Pin 8 Voltage = –5V, T = 25°C
110
1.4
ns
en
A
Shutdown Assert or Release Time (Note 9)
Pin 8 Voltage = –5V, T = 25°C
µs
SHDN
A
3
LT1204
AC CHARACTERISTICS TA = 25°C, V = ±15V, RF = RG = 1k, unless otherwise noted.
S
SYMBOL
PARAMETER
CONDITIONS
MIN
TYP
5.6
1000
40
MAX
UNITS
ns
t , t
Small-Signal Rise and Fall Time
Slew Rate (Note 10)
R = 150Ω, V = ±125mV
L
r
f
OUT
SR
R = 400Ω
L
400
V/µs
mV
ns
Channel Select Output Transient
Settling Time
All V = 0V, R = 400Ω, Input Referred
IN L
t
0.1%, V = 10V, R = 1k
70
S
OUT
L
All Hostile Crosstalk (Note 11)
Disable Crosstalk (Note 11)
Shutdown Crosstalk (Note 11)
All Hostile Crosstalk (Note 11)
Disable Crosstalk (Note 11)
Shutdown Crosstalk (Note 11)
Differential Gain (Note 12)
SO PCB #028, R = 100Ω, R = 10Ω
92
dB
L
S
SO PCB #028, Pin 11 Voltage = 0V, R = 100Ω, R = 50Ω
95
dB
L
S
SO PCB #028, Pin 12 Voltage = 0V, R = 100Ω, R = 50Ω
92
dB
L
S
PDIP PCB #029, R = 100Ω, R = 10Ω
76
dB
L
S
PDIP PCB #029, Pin 11 Voltage = 0V, R = 100Ω, R = 50Ω
81
dB
L
S
PDIP PCB #029, Pin 12 Voltage = 0V, R = 100Ω, R = 50Ω
76
dB
L
S
V = ±15V, R = 150Ω
0.04
0.04
%
%
S
L
V = ±5V, R = 150Ω
S
L
Differential Phase (Note 12)
V = ±15V, R = 150Ω
0.06
0.12
DEG
DEG
S
L
V = ±5V, R = 150Ω
S
L
The ● denotes specifications which apply over the specified operating
temperature range.
appearance of 5V at Pin 15 when Pin 9 goes from 5V to 0V. Pin 10
Voltage = 5V. Apply 0.5V DC to Pin 7 and measure the time for the
appearance of 5V at Pin 15 when Pin 9 goes from 0V to 5V. Pin 10
Voltage = 5V.
Note 1: Analog and digital inputs (Pins 1, 3, 5, 7, 9, 10, 11 and 12) are
protected against ESD and overvoltage with internal SCRs. For inputs
< ±6V the SCR will not fire, voltages above 6V will fire the SCRs and
the DC current should be limited to 50mA. To turn off the SCR the pin
voltage must be reduced to less than 2V or the current reduced to less
than 10mA.
Note 7: Apply 0.5V DC to Pin 1 and measure the time for the
disappearance of 5V at Pin 15 when Pin 11 goes from 5V to 0V.
Pins 9 and 10 are at 0V.
Note 8: Apply 0.5V DC to Pin 1 and measure the time for the
appearance of 5V at Pin 15 when Pin 11 goes from 0V to 5V.
Pins 9 and 10 are at 0V. Above a 1MHz toggle rate, ten reduces.
Note 2: A heat sink may be required depending on the power supply
voltage.
Note 3: Commercial grade parts are designed to operate over the
temperature range of –40°C to 85°C but are neither tested nor
guaranteed beyond 0°C to 70°C. Industrial grade parts specified and
tested over –40°C to 85°C are available on special request. Consult
factory.
Note 9: Apply 0.5V DC at Pin 1 and measure the time for the
appearance of 5V at Pin 15 when Pin 12 goes from 0V to 5V.
Pins 9 and 10 are at 0V. Then measure the time for the disappearance
of 5V DC to 500mV at Pin 15 when Pin 12 goes from 5V to 0V.
Note 10: Slew rate is measured at ±5V on a ±10V output signal while
operating on ±15V supplies with RF = 2k, RG = 220Ω and RL = 400Ω.
Note 4: T is calculated from the ambient temperature TA and power
J
dissipation PD according to the following formulas:
Note 11: V = 0dBm (0.223VRMS) at 10MHz on any 3 inputs with the
IN
LT1204CN: T = TA + (PD)(70°C/W)
4th input selected. For Disable crosstalk and Shutdown crosstalk all 4
inputs are driven simultaneously. A 6dB output attenuator is formed by
a 50Ω series output resistor and the 50Ω input impedance of the
HP4195A Network Analyzer. RF = RG = 1k.
J
LT1204CS: T = TA + (PD)(90°C/W)
J
Note 5: The supply current of the LT1204 has a negative temperature
coefficient. For more information see Typical Performance
Characteristics.
Note 12: Differential Gain and Phase are measured using a Tektronix
TSG120 YC/NTSC signal generator and a Tektronix 1780R Video
Measurement Set. The resolution of this equipment is 0.1% and 0.1°.
Five identical MUXs were cascaded giving an effective resolution of
0.02% and 0.02°.
Note 6: Apply 0.5V DC to Pin 1 and measure the time for the
appearance of 5V at Pin 15 when Pin 9 goes from 5V to 0V. Pin 10
Voltage = 0V. Apply 0.5V DC to Pin 3 and measure the time for the
appearance of 5V at Pin 15 when Pin 9 goes from 0V to 5V. Pin 10
Voltage = 0V. Apply 0.5V DC to Pin 5 and measure the time for the
4
LT1204
W U
TYPICAL AC PERFOR A CE
Measurements taken from SO Demonstration Board #028.
SMALL SIGNAL
–3dB BW (MHz)
SMALL SIGNAL
0.1dB BW (MHz)
SMALL SIGNAL
PEAKING (dB)
V (V)
S
A
V
R (Ω)
L
R (Ω)
F
R (Ω)
G
±15
±12
±5
1
150
1k
1.1k
1.6k
None
None
88.5
95.6
48.3
65.8
0.1
0
1
150
1k
976
1.3k
None
None
82.6
90.2
49.1
63.6
0.1
0.1
1
150
1k
665
866
None
None
65.5
68.2
43.6
42.1
0.1
0.1
±15
±12
±5V
±15
±12
±5
2
150
1k
787
887
787
887
75.7
82.2
45.8
61.3
0
0.1
2
150
1k
750
845
750
845
71.9
77.5
45.0
52.1
0
0
2
150
1k
590
649
590
649
58.0
62.1
32.4
42.7
0
0.1
10
10
10
150
1k
866
1k
95.3
110
44.3
47.4
28.7
30.9
0.1
0.1
150
1k
825
931
90.9
100
43.5
46.3
27.2
32.1
0
0.1
150
1k
665
750
73.2
82.5
37.2
39.3
22.1
27.8
0
0.1
TRUTH TABLE
CHANNEL
SELECTED
A1
A0
ENABLE
SHUTDOWN
0
0
1
1
0
1
0
1
1
1
1
1
1
1
1
1
V
IN0
V
IN1
V
IN2
V
IN3
X
X
X
X
0
1
0
High Z Output
Off
X
5
LT1204
U W
TYPICALPERFOR A CE CHARACTERISTICS
±12V Frequency Response, AV = 1
±5V Frequency Response, AV = 1
4
3
2
1
0
4
3
2
1
0
V = ±12V
V = ±5V
S
S
–20
–40
–60
–20
–40
–60
R = 150Ω
R = 976Ω
F
R = 150Ω
R = 655Ω
F
L
L
PHASE
PHASE
0
–80
0
–80
GAIN
GAIN
–1
–100
–1
–100
–2
–3
–4
–5
– 6
–120
–140
–160
–180
–200
–2
–3
–4
–5
–6
–120
–140
–160
–180
–200
1M
10M
100M
1G
1M
10M
100M
1G
FREQUENCY (Hz)
FREQUENCY (Hz)
1204 G01
1204 G04
±12V Frequency Response, AV = 2
±5V Frequency Response, A = 2
V
10
9
0
10
9
0
V = ±5V
V = ±12V
S
R
L
S
–20
–40
–60
–20
–40
–60
= 150Ω
R = 150Ω
R = 750Ω
F
L
PHASE
R = 590Ω
8
F
R
G
8
= 590Ω
R
G
= 750Ω
PHASE
7
7
6
5
–80
6
5
–80
GAIN
GAIN
–100
–100
4
3
2
1
0
–120
–140
–160
–180
–200
4
3
2
1
0
–120
–140
–160
–180
–200
1M
10M
100M
1G
1M
10M
100M
1G
FREQUENCY (Hz)
FREQUENCY (Hz)
1204 G05
1204 G02
±12V Frequency Response, AV = 10
±5V Frequency Response, A = 10
V
24
23
22
21
0
24
23
22
21
0
V = ±12V
V = ±5V
S
S
–20
–40
–60
–20
–40
–60
R
L
= 150Ω
R = 150Ω
L
R = 825Ω
R = 665Ω
F
R = 73.2Ω
G
F
R
G
= 90.9Ω
PHASE
PHASE
20
19
–80
20
19
–80
GAIN
GAIN
–100
–100
18
17
16
15
14
–120
–140
–160
–180
–200
18
17
16
15
14
–120
–140
–160
–180
–200
1M
10M
100M
1G
1M
10M
100M
1G
FREQUENCY (Hz)
FREQUENCY (Hz)
1204 G03
1204 G06
6
LT1204
U W
TYPICALPERFOR A CE CHARACTERISTICS
Maximum Undistorted Output
vs Frequency
Maximum Capacitive Load
vs Feedback Resistor
Total Harmonic Distortion
vs Frequency
0.1
10000
1000
100
25
20
R
L
= 1k
V = ±15V
V = ±15V
S
S
A = 2
R = 400Ω
R
= 1k
= 1k
V
T
A
L
L
= 25°C
R = R = 1k
R
FB
F
G
≤ 5dB PEAKING
15
10
5
V = 6V
O RMS
0.01
A = 10
V
V = ±5V
S
V = ±15V
S
V = 1V
O RMS
A = 1
V
A = 2
V
0.001
10
0
10
100
1k
FREQUENCY (Hz)
10k
100k
0
1
2
3
1
10
FREQUENCY (MHz)
100
FEEDBACK RESISTOR (kΩ)
1204 G08
1204 G07
1204 G09
±5V All Hostile Crosstalk
vs Frequency
All Hostile Crosstalk vs Frequency,
Various Source Resistance
±15V All Hostile Crosstalk
vs Frequency
–30
–40
–20
–30
–20
–30
V = ±15V
R = 100Ω
L
V = ±5V
R = 100Ω
L
V = ±15V
S
R = 100Ω
L
S
S
R = R = 1k
R = R = 1k
R = R = 1k
F G
DEMO PCB #028
F
G
F
G
–40
–40
–50
R
S
= 0Ω
R
S
= 0Ω
–50
–50
–60
DEMO PCB #028
DEMO PCB #028
–70
–60
–60
–70
–70
–80
R
= 75Ω
S
–90
–80
–80
R
= 37.5Ω
= 10Ω
S
CH1
ANY CHANNEL
R
S
–90
–90
–100
–110
–120
–130
R
S
= 0Ω
CH4
CH3
–100
–110
–120
–100
–110
–120
CH2
1
10
FREQUENCY (MHz)
100
1
10
FREQUENCY (MHz)
100
1
10
FREQUENCY (MHz)
100
1204 G10
1204 G11
1204 G12
Amplifier Output Impedance
vs Frequency
Disable and Shutdown Crosstalk
vs Frequency
Spot Noise Voltage and Current
vs Frequency
1000
100
10
–20
–30
100
10
1
V = ±15V
S
V = ±15V
S
R = 100Ω
L
–i
n
R = R = 1k
F
R
S
G
–40
= 50Ω
–50
DEMO PCB #028
ALL CHANNELS DRIVEN
–60
–70
e
n
–80
SHUTDOWN CROSSTALK
R
FB
= R = 2k
G
–90
1
–100
–110
–120
DISABLE CROSSTALK
R
FB
= R = 750Ω
G
+i
n
0.1
1
10
100
1M
FREQUENCY (Hz)
10M
100M
10
100
1k
FREQUENCY (Hz)
10k
100k
10k
100k
FREQUENCY (MHz)
1204 G13
1204 G15
1204 G14
7
LT1204
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TYPICAL PERFORMANCE CHARACTERISTICS
Disabled Output Impedance
vs Frequency
Maximum Channel Switching
Rate vs Pin 8 Voltage
Output Disable V-I Characteristic
100
10
1
0
–1
–2
–3
V = ±15V
V
= 1V
DC
V = ±15V
S
IN
= 100Ω
S
200
150
100
50
R = R = 1k
R
R = R = 1k
F
G
L
F
G
R
FB
= R = 1k
G
–4
–5
0
–50
–100
–150
–200
SLOPE = 1/18k
–6
–7
–8
0
1.5
2.0
3.0
–5 –4 –3 –2 –1
0
1
2
3
4
5
1.0
2.5
3.5
4.0
1k
10k
100k
1M
10M
100M
OUTPUT VOLTAGE (V)
CHANNEL SWITCHING RATE (MHz)
FREQUENCY (Hz)
1204 G17
1204 G16
1204 G18
Input Voltage Range
vs Supply Voltage
Input Voltage Range
vs Pin 8 Voltage
Power Supply Rejection
vs Frequency
70
60
50
40
30
20
10
0
V = ±15V
V = ±15V
A = 1
V
PIN 8 = 0V
6
4
6
4
S
S
R
FB
= R = 1k
G
25°C
POSITIVE
–55°C
125°C
2
2
NEGATIVE
0
0
–55°C, 25°C, 125°C
125°C
–2
–4
–6
–2
–4
–6
25°C
–55°C
–10
12
14
16
10k
100k
1M
FREQUENCY (Hz)
10M
100M
0
–1 –2 –3 –4 –5 –6 –7 –8 –9
2
4
6
8
10
VOLTAGE ON PIN 8 (V)
SUPPLY VOLTAGE (±V)
1204 G19
1204 G20
1204 G21
Output Saturation Voltage
vs Temperature
Output Short-Circuit Current
vs Temperature
Settling Time to 10mV
vs Output Step
+
V
80
70
60
50
40
30
10
8
V = ±15V
R
L
= ∞
S
R = R = 1k
F
G
–0.5
–1.0
6
4
2
0
–2
–4
–6
–8
–10
1.0
0.5
–
V
50
TEMPERATURE (°C)
100 125
–50 –25
0
25
75
40
60
SETTLING TIME (ns)
30
50
70
80
–50
0
25
50
75 100 125
–25
TEMPERATURE (°C)
1204 G22
1204 G24
1204 G23
8
LT1204
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TYPICALPERFOR A CE CHARACTERISTICS
Settling Time to 1mV
vs Output Step
Enabled Supply Current
vs Supply Voltage
Disabled and Shutdown Supply
Current vs Supply Voltage
22
21
20
19
18
17
16
15
14
13
12
22
21
20
19
18
17
16
15
2
10
8
V = ±15V
S
R = R = 1k
F
G
6
–55°C
25°C
125°C
4
2
25°C
0
–55°C
–2
–4
–6
–8
–10
125°C
I
–55°C, 25°C, 125°C
SHDN
1
0
0
2
4
6
8
10 12 14 16 18
0
2
4
6
8
10 12 14 16 18 20
14
SUPPLY VOLTAGE (±V)
0
2
4
6
8
10 12
16 18
SUPPLY VOLTAGE (±V)
SETTLING TIME (µs)
1204 G26
1205 G25
1204 G27
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Logic Inputs
specified over a very wide range of conditions. An advan-
tage of the current feedback topology used in the LT1204
is well-controlled frequency response. In all cases of the
performance table, the peaking is 0.1dB or less. If more
peaking can be tolerated, larger bandwidths can be
obtained by lowering the feedback resistor. For gains of
2 or less, the 0.1dB bandwidth is greater than 30MHz for
all loads and supply voltages.
The logic inputs of the LT1204 are compatible with all 5V
logic. All pins have ESD protection (>2kV), and shorting
them to 12V or 15V will cause excessive currents to flow.
Limit the current to less than 50mA when driving the logic
above 6V.
Power Supplies
At high gains (low values of RG) the disabled output
resistance drops slightly due to loading of the internal
buffer amplifier as discussed in Multiplexer Expansion.
The LT1204 will operate from ±5V (10V total) to ±15V
(30V total) and is specified over this range. It is not
necessary to use equal value supplies, however, the offset
voltage and inverting input bias current will change. The
offset voltage changes about 600µV per volt of supply
mismatch.Theinvertingbias currentchanges about2.5µA
per volt of supply mismatch. The power supplies should
be bypassed with quality tantalum capacitors.
Small-Signal Rise Time, AV = 2
Feedback Resistor Selection
The small-signal bandwidth of the LT1204 is set by the
external feedback resistors and internal junction capaci-
tors. As a result the bandwidth is a function of the supply
voltage, the value of the feedback resistor, the closed-
loop gain and the load resistor. These effects are outlined
in the resistor selection guide of the Typical AC Perfor-
mancetable.Bandwidths rangeas highas 95MHzandare
1204 AI01
V = ±15V RF = 1k
S
RL = 150Ω
RG = 1k
9
LT1204
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Large-Signal Transient Response
Capacitance on the Inverting Input
Current feedback amplifiers require resistive feedback
from the output to the inverting input for stable operation.
Take care to minimize the stray capacitance between the
output and the inverting input. Capacitance on the invert-
ing input to ground will cause peaking in the frequency
response and overshoot in the transient response.
Capacitive Loads
The LT1204 can drive capacitive loads directly when the
proper value of feedback resistor is used. The graph of
Maximum Capacitive Load vs Feedback Resistor should
be used to select the appropriate value. The value shown
is for 5dB peaking when driving a 1k load at a gain of 2.
This is a worst-case condition. The amplifier is more
stable at higher gains and driving heavier loads. Alterna-
tively, a small resistor (10Ω to 20Ω) can be put in series
with the output to isolate the capacitive load from the
amplifier output. This has the advantage that the ampli-
fier bandwidth is only reduced when the capacitive load
is present. The disadvantage is that the gain is a function
of load resistance.
1204 AI02
V = ±15V
AV = 2
RF = 1k
RG = 1k
RL = 400Ω
S
Large-Signal Transient Response
Slew Rate
The slew rate of the current feedback amplifier on the
LT1204 is not independent of the amplifier gain the way
slewrateis inatraditionalopamp.This is becauseboththe
input and the output stage have slew rate limitations. In
high gain settings the signal amplitude between the nega-
tive input and any driven positive input is small and the
overall slew rate is that of the output stage. For gains less
than 10, the overall slew rate is limited by the input stage.
1204 AI03
V = ±15V
A = 10
V
RF = 910Ω
RG = 100Ω
RL = 400Ω
S
Switching Characteristics and Pin 8
Switching between channels is a “make-before-break”
condition where both inputs are on momentarily. The
buffers isolate the inputs when the “make-before-break”
switching occurs. The input with the largest positive
voltage determines the output level. If both inputs are
equal, there is only a 40mV error at the input of the CFA
during the transition. The reference adjust (Pin 8) allows
the user to trade off positive input voltage range for
switching time. For example, on ±15V supplies, setting
the voltage on Pin 8 to –6.8V reduces the switching
transienttoa50ns duration,andreduces thepositiveinput
range from 6V to 2.35V. The negative input range remains
unchangedat–6V.Whenswitchingvideo“inpicture,”this
short transient is imperceptible even on high quality
The input slew rate of the LT1204 is approximately 135V/µs
and is set by internal currents and capacitances. The
output slew rate is set by the value of the feedback
resistors andtheinternalcapacitances.Atagainof10with
a 1k feedback resistor and ±15 supplies, the output slew
rate is typically 1000V/µs. Larger feedback resistors will
reduce the slew rate as will lower supply voltages, similar
to the way the bandwidth is reduced.
The graph, Maximum Undistorted Output vs Frequency,
relates the slew rate limitations to sinusoidal inputs for
various gain configurations.
10
LT1204
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Competitive MUXs
monitors.Thereferencepinhas noeffectwhentheLT1204
is operating on ±5V, and should be grounded. On supply
voltages above ±8V, the range of voltages for Pin 8 should
be between –6.5V and –7.5V. Reducing Pin 8 voltage
below –7.5V turns “on” the “off” tee switch, and the
isolation between channels is lost.
CMOS MUX
Channel-to-Channel Switching
BIPOLAR
MUX
A0 PIN 9
1204 AI06
VIN0 AND VIN1 CONNECTED TO 2MHz SINEWAVE
Crosstalk
VOUT PIN 15
The crosstalk, or more accurately all hostile crosstalk, is
measured by driving a signal into any three of the four
inputs and selecting the 4th input with the logic control.
This 4th input is either shorted to ground or terminated in
an impedance. All hostile crosstalk is defined as the ratio
indecibelofthesignalattheoutputoftheCFAtothesignal
on the three driven inputs, and is input-referred. Disable
crosstalk is measured with all four inputs driven and the
part disabled. Crosstalk is critical in many applications
where video multiplexers are used. In professional video
systems, a crosstalk figure of –72dB is a desirable
specification.
1204 AI04
V
IN0 AND VIN1 CONNECTED TO 2MHz SINEWAVE
PIN 8 VOLTAGE = –6.8V, V = ±15V
S
Transient at Input Buffer
A0 PIN 9
The key to the outstanding crosstalk performance of the
LT1204 is the use of tee switches (see Figure 1). When the
tee switch is on (Q2 off) Q1 and Q3 are a pair of emitter
followers with excellent AC response for driving the CFA.
VIN0 PIN 1
+
1204AI05
V
SWITCHING BETWEEN VIN0 AND V
IN1
RS = 50Ω, VREF = –6.8V, V ±15V
S
I
1
Q3
Competitive video multiplexers built in CMOS are bidirec-
tional and suffer from poor output-to-input isolation and
cause transients to feed to the inputs. CMOS MUXs have
beenbuiltwith“break-before-make”switches toeliminate
thetalkingbetweenchannels, butthesesufferfromoutput
glitches large enough to interfere with sync circuitry.
Multiplexers built on older bipolar processes that switch
lateralPNPtransistors takeseveralmicroseconds tosettle
and blur the transition between pictures.
V
IN0
Q1
+
–
V
OUT
TO LOGIC
Q2
CFA
–
V
R
F
FB
I
2
R
G
–V
1204 F01
Figure 1. Tee Switch
11
LT1204
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When the decoder turns off the tee switch (Q2 on) the
emitter base junctions of Q1 and Q3 become reverse-
biased while Q2 emitter absorbs current from I1. Not only
dothereverse-biasedemitterbasejunctions providegood
isolation, but any signal at VIN0 coupling to Q1 emitter is
further attenuated by the shunt impedance of Q2 emitter.
Current from I2 is routed to any on switch.
bers. A graph of all hostile crosstalk for both the PDIP and
SO packages is shown. It has been found empirically from
these PC boards that capacitive coupling across the pack-
age of greater than 3fF (0.003pF) will diminish the rejec-
tion, and it is recommended that this proven layout be
copied into designs. The key to the success of the SO PC
board #028 is the use of a ground plane guard around Pin
13, the feedback pin.
Crosstalk performance is a strong function of the IC
package, the PC board layout as well as the IC design. The
die layout utilizes grounds between each input to isolate
adjacent channels, while the output and feedback pins are
on opposite sides of the die from the input. The layout of
a PC board that is capable of providing –90dB all hostile
crosstalk at 10MHz is not trivial. That level corresponds to
a 30µV output below a 1V input at 10MHz. A demonstra-
tionboardhas beenfabricatedtoshowthecomponentand
ground placement required to attain these crosstalk num-
PDIP PC Board #029, Component Side
GND
V–
V+
VOUT
VIN0
C1
+
ENABLE
R1
RO
C2
C3
+
All Hostile Crosstalk
U1
VIN1
–20
RF
V = ±15V
S
V
IN0
= GND
V
R
= 0dBm
IN1,2,3
= 100Ω
–40
–60
C4
R3
R0
S/D
REF
R6
PDIP
DEMO PCB #029
VIN2
VIN3
R2
–80
SO
DEMO PCB #028
R1
–100
–120
(408) 432-1900
LT1204 VIDEO MUX
DEMONSTRATION BOARD
1
10
FREQUENCY (MHz)
100
1204 AI09
1204 AI07
12
LT1204
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SOL PC Board #028, Component Side
GND
V–
V+
VOUT
VIN0
VIN1
ENABLE
A1
C2
C4
C1
RO
U1
RF
R3
C3
RG
R2
A0
R1
VIN2
VIN3
S/ D
(408) 432-1900
LT1204 VIDEO MUX
DEMONSTRATION BOARD
REF
1204 AI08
13
LT1204
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Demonstration PC Board Schematic
–
+
GND
V
V
+
+
C1
4.7µF
C2
0.1µF
1
2
3
4
5
6
7
8
16
+
V
V
V
IN0
IN0
R
O
75Ω
15
GND
V
O
C3
4.7µF
14
13
12
11
10
9
C4
0.1µF
R
750Ω
–
F
V
IN1
V
IN1
V
R
G
750Ω
GND
FB
LT1204
SHUTDOWN
ENABLE
A1
V
IN2
SHDN
ENABLE
A1
V
IN2
R3
10k
GND
RESISTORS R1, R2 AND R3 ARE PULL-DOWN
AND PULL-UP RESISTORS FOR THE LOGIC
AND ENABLE PINS. THEY MAY BE OMITTED
IF THE LT1204 IS DRIVEN FROM TTL LEVELS
OR FROM 5V CMOS.
V
IN3
V
IN3
REF
A0
A0
R1
R2
10k
10k
REF
L1204 AI10
All Hostile Crosstalk Test Setup*
Alternate All Hostile Crosstalk Setup*
HP4195A
HP4195A
NETWORK ANALYZER
NETWORK ANALYZER
OSC
50Ω
REF
50Ω
V
50Ω
OSC
50Ω
REF
50Ω
V
IN
50Ω
IN
50Ω
50Ω
SPLITTER
SPLITTER
10Ω
1
16
+
15V
V
IN0
V
10Ω
1
2
3
4
5
6
7
8
16
15
14
13
12
11
10
9
+
50Ω
15V
V
V
2
3
4
5
6
7
8
15
14
13
12
11
10
9
IN0
GND
V
O
50Ω
GND
V
O
–
1k
V
IN1
V
–15V
–
1k
1k
V
IN1
V
–15V
GND
FB
1k
50Ω
LT1204
GND
FB
V
IN2
SHDN
ENABLE
A1
10k
LT1204
V
IN2
SHDN
ENABLE
A1
10k
GND
50Ω
GND
V
IN3
*SEE PC BOARD LAYOUT
V
IN3
REF
A0
*SEE PC BOARD LAYOUT
50Ω
50Ω
REF
A0
1204 AI11
1204 AI12
14
LT1204
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Multiplexer Expansion Pin 11 and Pin 12
The multiplexer uses a circuit to ensure the disabled
amplifiers do not load or alter the cable termination. When
the LT1204 is disabled (Pin 11 low) the output stage is
turned off and an active buffer senses the output and
drives the feedback pin to the CFA (Figure 2). This boot-
straps the feedback resistors and raises the true output
impedance of the circuit. For the condition where RF = RG
= 1k, the Disable Output Resistance is typically raised to
25k and drops to 20k for AV = 10, RF = 2k and RG = 222Ω
due to loading of the feedback buffer. Operating the
Disable feature with RG < 100Ω is not recommended.
To expand the number of MUX inputs, LT1204s can be
paralleled by shorting their outputs together. The multi-
plexer disable logic has been designed to prevent shoot-
through current when two or more amplifiers have their
outputs shorted together. (Shoot-through current is a
spike of power supply current caused by both amplifiers
being on at once.)
Monitoring Supply Current Spikes
+
V
TEK
TO SCOPE
CT-1
V
TEE SWITCH
TEE SWITCH
IN0
A = +1
1
3
5
7
13
V
+
+
+
+
–
16
75Ω
15
LT1204
EN
V
IN1
+
–
11
V
OUT
14
–
CFA
“OFF”
V
IN2
TEE SWITCH
TEE SWITCH
V
1k
75Ω
V
IN3
R
F
1k
FB
74HC04
5V
O
75Ω
R
G
CABLE
75Ω
–
V
+
OSCILLATOR
V
16
75Ω
1
3
5
7
13
+
+
+
+
–
11
EN
LT1204
“ON”
75Ω
15
LT1204
1204 F02
14
–
V
Figure 2. Active Buffer Drives FB Pin 13
1k
1204 AI13
1k
A shutdown feature (Pin 12 low) reduces the supply
current to 1.5mA and lowers the power dissipation
when the LT1204 is not in use. If the part is shut down,
thebootstrappingis inoperativeandthefeedbackresis-
tors will load the output. If the CFA is operated at a gain
of +1, however, the feedback resistor will not load the
output even in shutdown because there is no resistive
path to ground, but there will be a –6dB loss through
the cable system.
Timing and Supply Current Waveforms
74HC04
OUTPUT
5V/DIV
OSCILLATOR
5V/DIV
VOUT
1V/DIV
A frequency response plot shows the effect of using the
disable feature versus using the shutdown feature. In
this example four LT1204s were connected together at
theiroutputs forminga16-to-1MUX. Theplotshows the
effect of the bootstrapping circuit that eliminates the
IS
10mA/DIV
1204 AI14
15
LT1204
PPLICATI
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improper cable termination due to feedback resistors
loading the cable.
For a 64-to-1 MUX we need sixteen LT1204s. The
equivalent load resistance due to the feedback resistor
R
EQ in Disable is 25k/15 = 1.67k. See Figure 3.
The limit to the number of expanded inputs is set by the
acceptable error budget of the system.
75R
EQ
V =
, V = 0.489V
O
O
75(75) + 150R
EQ
16-to-1 MUX Response Using Disable vs Shutdown
4
V = ±15V
This voltage represents a 2.1% loading error. If the
shutdown feature is used instead of the disable feature,
then the LT1204 could expand to only an 8-to-1 MUX for
the same error.
S
R
L
= 100Ω
R = R = 1k
F
G
2
0
DISABLE
SHUTDOWN
As a practical matter the gain error at frequency is also
set by capacitive loading. The disabled output capaci-
tance of the LT1204 is about 8pF, and in the case of
sixteen LT1204s, it would represent a 128pF load. The
combination of 1.67k and 128pF correspond to about a
0.3dB roll-off at 5MHz.
–2
–4
–6
1
10
100
FREQUENCY (MHz)
1204 AI15
OFF
75Ω
LT1204
16-to-1 Multiplexer All Hostile Crosstalk
CABLE
–20
V
OUT
V = ±15V
S
R
= 100Ω
L
ON
R = R = 1k
F
G
75Ω
–40
–60
R
S
= 0
75Ω
1V
LT1204
SHUTDOWN
CROSSTALK
–80
V
75Ω
DISABLE
CROSSTALK
OUT
–100
–120
1V
R
EQ
75Ω
1
10
FREQUENCY (MHz)
100
1204 F03
1204 AI16
Figure 3. Equivalent Loading Schematic
16
LT1204
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Programable Gain Amplifier (PGA)
by 1, 0.5, 0.25 and 0.125 to form an amplifier with a gain
of 16, 8, 4, 2, when LT1204 #1 is selected. LT1204 #2
is connected to the same attenuator. When enabled
(LT1204#1disabled),itresults ingainof1,0.5,0.25and
0.125. The wide input common mode range of the
Two LT1204s and seven resistors make a Programable
Gain Amplifier with a 128-to-1 gain range. The gain is
proportional to 2N where N is the 3-bit binary value of the
select logic. An input attenuator alters the input signal
LT1204 is needed to accept inputs of 8V .
P-P
Programable Gain Amplifier Accepts Inputs
4-Input Differential Receiver
from 62.5mVP-P to 8V
P-P
V
IN
= 62.5mV TO 8V
P-P P-P
LT1204s can be connected inverting and noninverting as
shown to make a 4-input differential receiver. The receiver
can be used to convert differential signals sent over a low
cost twisted pair to a single-ended output or used in video
loop-thruconnections. Thelogicinputs A0andA1are tied
together because the same channels are selected on each
LT1204. By using the Disable feature, the number of
differential inputs can be increased by adding pairs of
LT1204s andtyingtheoutputs ofthenoninvertingLT1204s
(#1) together. Switching transients are reduced in this
receiver because the transient from LT1204 #2 subtracted
from the transient of LT1204 #1.
1
3
5
7
13
+
+
+
+
–
LT1204
#1
499Ω
249Ω
124Ω
1.5k
124Ω
100Ω
V
= 1V
P-P
OUT
1
+
3
+
5
LT1204
#2
+
7
13
+
–
1.5k
1204 TA03
4-Input Differential Receiver
A0 A1 SHDN EN
TWISTED PAIR
+
+
+
+
–
IN 1
IN 2
IN 3
IN 4
A0
A1
SHDN
68Ω
68Ω
75Ω
EN
1k
V
OUT
LT1204
#1
75Ω
CABLE
1k*
1k
1k*
1k*
+
+
+
+
–
–IN 1
–IN 2
–IN 3
–IN 4
A0
A1
SHDN
1k*
*OPTIONAL
EN
1k
LT1204
#2
1204 TA04
1k
17
LT1204
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Differential Receiver Switching Waveforms
Differential Receiver Response
V = ±15V
S
20
0
R
L
= 100Ω
CABLE
OUTPUT
DIFFERENTIAL MODE RESPONSE
–20
–40
–60
LT1204
#2 OUTPUT
COMMON MODE RESPONSE
A0 PIN 9
10k
100k
1M
10M
100M
1204 TA05
FREQUENCY (Hz)
1204 TA06
4-Input Twisted-Pair Driver
and drive the video signal on to the twisted pair. The circuit
uses anLT1227currentfeedbackamplifierconnectedwith
a gain of –2, and an LT1204 with a gain of 2. The 47Ω
resistors back-terminate the low cost cable in its charac-
teristic impedance to prevent reflections. The receiver for
the differential signal is an LT1193 connected for a gain of
2. Resistors R1, R2 and capacitors C1, C2 are used for
cable compensation for loss through the twisted pair.
Alternately, a pair of LT1204s can be used to perform the
differential to single-ended conversion.
It is possible to send and receive color composite video
signals appreciable distances on a low cost twisted pair.
The cost advantage of this technique is significant. Stan-
dard 75Ω RG-59/U coaxial cable cost between 25¢ and
50¢ per foot. PVC twisted pair is only pennies per foot.
Differential signal transmission resists noise because the
interference is present as a common mode signal. The
LT1204 can select one of four video cameras for instance,
Multiburst Pattern Passed Through 1000 Feet of Twisted Pair,
No Cable Compensation
Multiburst Pattern Passed Through 1000 Feet of Twisted Pair,
with Cable Compensation
OUTPUT
INPUT
INPUT
OUTPUT
1204 TA08
1204 TA09
18
LT1204
U
Dimensions in inches (millimeters) unless otherwise noted.
PACKAGE DESCRIPTIO
N Package
16-Lead PDIP (Narrow 0.300)
(LTC DWG # 05-08-1510)
0.770*
(19.558)
MAX
14
12
10
9
15
13
11
16
0.255 ± 0.015*
(6.477 ± 0.381)
2
1
3
4
6
8
5
7
0.300 – 0.325
0.130 ± 0.005
0.045 – 0.065
(7.620 – 8.255)
(3.302 ± 0.127)
(1.143 – 1.651)
0.020
(0.508)
MIN
0.065
0.009 – 0.015
(1.651)
TYP
(0.229 – 0.381)
+0.035
–0.015
0.325
0.125
0.018 ± 0.003
0.100 ± 0.010
(2.540 ± 0.254)
+0.889
–0.381
(3.175)
MIN
(0.457 ± 0.076)
8.255
(
)
*THESE DIMENSIONS DO NOT INCLUDE MOLD FLASH OR PROTRUSIONS.
MOLD FLASH OR PROTRUSIONS SHALL NOT EXCEED 0.010 INCH (0.254mm)
N16 1197
SW Package
16-Lead Plastic Small Outline (Wide 0.300)
(LTC DWG # 05-08-1620)
0.398 – 0.413*
(10.109 – 10.490)
15 14
12
10
11
9
16
13
0.394 – 0.419
(10.007 – 10.643)
NOTE 1
2
3
5
7
8
1
4
6
0.291 – 0.299**
(7.391 – 7.595)
0.037 – 0.045
(0.940 – 1.143)
0.093 – 0.104
(2.362 – 2.642)
0.010 – 0.029
(0.254 – 0.737)
× 45°
0° – 8° TYP
0.050
(1.270)
TYP
0.004 – 0.012
(0.102 – 0.305)
0.009 – 0.013
(0.229 – 0.330)
NOTE 1
0.014 – 0.019
0.016 – 0.050
(0.356 – 0.482)
TYP
(0.406 – 1.270)
NOTE:
1. PIN 1 IDENT, NOTCH ON TOP AND CAVITIES ON THE BOTTOM OF PACKAGES ARE THE MANUFACTURING OPTIONS.
THE PART MAY BE SUPPLIED WITH OR WITHOUT ANY OF THE OPTIONS
S16 (WIDE) 0396
*DIMENSION DOES NOT INCLUDE MOLD FLASH. MOLD FLASH SHALL NOT EXCEED 0.006" (0.152mm) PER SIDE
**DIMENSION DOES NOT INCLUDE INTERLEAD FLASH. INTERLEAD FLASH SHALL NOT EXCEED 0.010" (0.254mm) PER SIDE
Information furnished by Linear Technology Corporation is believed to be accurate and reliable.
However, no responsibility is assumed for its use. Linear Technology Corporation makes no represen-
tationthattheinterconnectionofits circuits as describedhereinwillnotinfringeonexistingpatentrights.
19
LT1204
TYPICAL APPLICATION
U
4-Input Twisted-Pair Driver/Receiver
V
IN0
+
+
+
+
–
V
IN1
75Ω
V
IN2
LT1204
V
IN3
1000 FT OF
TWISTED PAIR
1k
47Ω
47Ω
+
1k
91Ω
75Ω
2k
LT1193
–
+
–
–
300Ω
1204 TA07
LT1227
+
18Ω
390Ω
300pF
300Ω
200Ω
680pF
RELATED PARTS
PART NUMBER
LT1203/LT1205
LT1259/LT1260
LT1675
DESCRIPTION
COMMENTS
150MHz Video Multiplexer
High Speed, but No Cable Driving
Low Cost, with Shutdown
Dual and Triple Current Feedback Amplifiers
RGB Multiplexer with Current Feedback Amplifiers
Very High Speed, Pixel Switching
1204fas, sn1204 LT/TP 0898 2K REV A • PRINTED IN USA
LINEAR TECHNOLOGY CORPORATION 1993
LinearTechnology Corporation
1630 McCarthy Blvd., Milpitas, CA 95035-7417
20
●
●
(408)432-1900 FAX:(408)434-0507 www.linear-tech.com
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