LT1946A [Linear]
2.7MHz Boost DC/DC Converter with 1.5A Switch and Soft-Start; 2.7MHz升压型DC / DC转换器,具有1.5A开关和软启动型号: | LT1946A |
厂家: | Linear |
描述: | 2.7MHz Boost DC/DC Converter with 1.5A Switch and Soft-Start |
文件: | 总12页 (文件大小:314K) |
中文: | 中文翻译 | 下载: | 下载PDF数据表文档文件 |
LT1946A
2.7MHz Boost DC/DC
Converter with 1.5A Switch
and Soft-Start
U
FEATURES
DESCRIPTIO
■
1.5A, 36V Internal Switch
The LT®1946A is a fixed frequency step-up DC/DC con-
verter containing an internal 1.5A, 36V switch. Capable of
generating 12V at 430mA from a 5V input, the LT1946A is
ideal for powering large TFT-LCD panels. The LT1946A
switches at 2.7MHz, allowing the use of tiny, low profile
inductors and low value ceramic capacitors. Loop com-
pensationcanbeeitherinternalorexternal, givingtheuser
flexibility in setting loop compensation and allowing opti-
mized transient response with low ESR ceramic output
capacitors.Soft-startiscontrolledwithanexternalcapaci-
tor which determines the input current ramp rate during
start up. The 8-lead MSOP package and high switching
frequency ensure a low profile overall solution less than
1.1mm high.
■
2.7MHz Switching Frequency
■
Integrated Soft-Start Function
Adjustable Output from VIN to 35V
■
■
Low VCESAT Switch: 300mV at 1.5A (Typical)
■
12V at 430mA from a 5V Input
■
Small Thermally Enhanced 8-Lead MSOP Package
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APPLICATIO S
■
TFT-LCD Bias Supplies
■
GPS Receivers
■
DSL Modems
Local Power Supply
■
, LTC and LT are registered trademarks of Linear Technology Corporation.
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TYPICAL APPLICATIO
L1
D1
Efficiency
2.2µH
V
OUT
V
IN
12V
90
5V
430mA
6
5
SW
R1
85
80
75
70
65
60
55
50
V
IN
182k
3
1
OFF ON
SHDN
LT1946A
2
7
C1
FB
2.2µF
C2
2.2µF
V
C
COMP
GND*
4
R
C
SS
27.4k
R2
21k
8
C
C
C
SS
100nF
270pF
1946A TA01
C1: 2.2µF, X5R or X7R, 6.3V
C2: 2.2µF, X5R or X7R, 16V
D1: MICROSEMI UPS120 OR EQUIVALENT
L1: SUMIDA CR43-2R2
* EXPOSED PAD MUST ALSO BE GROUNDED
0
100
200
300
400
500
LOAD CURRENT (mA)
Figure 1. 5V to 12V, 430mA Step-Up DC/DC Converter
1946A TA01
sn1946a 1946afs
1
LT1946A
W W
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ABSOLUTE AXI U RATI GS
PACKAGE/ORDER I FOR ATIO
(Note 1)
ORDER PART
VIN Voltage .............................................................. 16V
SW Voltage ................................................–0.4V to 36V
FB Voltage .............................................................. 2.5V
Current into FB Pin ............................................... ±1mA
SHDN Voltage .......................................................... 16V
Maximum Junction Temperature .......................... 125°C
Operating Temperature
Range (Note 2) ....................................... –40°C to 85°C
Storage Temperature Range ................. –65°C to 150°C
Lead Temperature (Soldering, 10 sec).................. 300°C
TOP VIEW
NUMBER
V
1
2
3
4
8 SS
7 COMP
C
FB
SHDN
GND
LT1946AEMS8E
6 V
5 SW
IN
MS8E PACKAGE
8-LEAD PLASTIC MSOP
EXPOSED PAD IS GROUND
(MUST BE SOLDERED TO PCB)
MS8E PART
MARKING
LTYZ
TJMAX = 125°C, θJA = 40°C/W,
θJC = 10°C/W
Consult LTC Marketing for parts specified with wider operating temperature ranges.
ELECTRICAL CHARACTERISTICS
The ● denotes the specifications which apply over the full operating
temperature range, otherwise specifications are at TA = 25°C. VIN = 3V, VSHDN = VIN unless otherwise noted. (Note 2)
PARAMETER
CONDITIONS
MIN
TYP
MAX
2.6
UNITS
Minimum Operating Voltage
Maximum Operating Voltage
Feedback Voltage
2.45
V
V
16
1.23
1.22
1.25
1.27
1.27
V
V
●
●
FB Pin Bias Current
V
= 1.25V (Note 3)
20
40
120
nA
µmhos
V/V
FB
Error Amp Transconductance
Error Amp Voltage Gain
Quiescent Current
∆I = 2µA
300
3.6
0
V
V
= 2.5V, Not Switching
5
1
mA
SHDN
SHDN
Quiescent Current in Shutdown
Reference Line Regulation
Switching Frequency
= 0V, V = 3V
µA
IN
2.6V ≤ V ≤ 16V
0.01
2.7
0.05
%/V
IN
2.4
2.3
3
3.1
MHz
MHz
●
Switching Frequency in Foldback
Maximum Duty Cycle
V
= 0V
0.85
80
MHz
%
FB
●
●
73
Switch Current Limit
(Note 4)
1.5
2.1
240
0.01
4
3.1
340
1
A
Switch V
I
= 1A
SW
mV
µA
µA
V
CESAT
Switch Leakage Current
Soft-Start Charging Current
SHDN Input Voltage High
SHDN Input Voltage Low
SHDN Pin Bias Current
V
V
= 5V
SW
SS
= 0.5V
2.5
2.4
6
0.5
V
V
V
= 3V
= 0V
16
0
32
0.1
µA
µA
SHDN
SHDN
Note 1: Absolute Maximum Ratings are those values beyond which the life
of a device may be impaired.
temperature range are assured by design, characterization and correlation
with statistical process controls.
Note 2: The LT1946AE is guaranteed to meet performance specifications
from 0°C to 70°C. Specifications over the –40°C to 85°C operating
Note 3: Current flows out of the FB pin.
Note 4: Current limit guaranteed by design and/or correlation to static test.
Current limit is independent of duty cycle and is guaranteed by design.
sn1946a 1946afs
2
LT1946A
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TYPICAL PERFOR A CE CHARACTERISTICS
Feedback Pin Voltage
Oscillator Frequency
Current Limit
1.28
3000
2700
2400
2100
1800
1500
1200
900
2.6
2.4
2.2
2.0
1.8
1.6
1.4
1.2
1.0
0.8
0.6
0.4
0.2
0
1.27
1.26
1.25
1.24
1.23
1.22
1.21
1.20
T
= –30°C
T
T
= 100°C
= 25°C
A
A
A
600
300
0
–50 –25
0
25
50
75 100 125
0
0.2
0.4
0.6
0.8
1
1.2
–50 –25
0
25
50
75 100 125
TEMPERATURE (°C)
FEEDBACK VOLTAGE (V)
TEMPERATURE (°C)
1946A G01
1946A G02
1946A G03
Switching Waveforms for
Figure 1 Circuit
Switch Saturation Voltage
Quiescent Current
0.35
0.30
0.25
0.20
0.15
0.10
0.05
0
4.0
3.8
3.6
3.4
3.2
3.0
2.8
2.6
2.4
2.2
VOUT
100mV/DIV
AC COUPLED
VSW
10V/DIV
0V
ILI
0.5A/DIV
100ns/DIV
1946A G06
0
0.2 0.4 0.6 0.8
1
1.2 1.4 1.6
–50 –25
0
25
50
75 100 125
SWITCH CURRENT (A)
TEMPERATURE (°C)
1946A G04
1946A G05
Transient Response for
Figure 1 Circuit
Start-Up Waveforms for
Figure 1 Circuit
VOUT
100mV/DIV
AC COUPLED
VOUT
2V/DIV
IIN
200mA/DIV
0A
ILI
0.5A/DIV
250mA
ILOAD
5V
0V
VSHDN
150mA
50µs/DIV
1946A G07
RLOAD = 250Ω
1ms/DIV
1946A G08
sn1946a 1946afs
3
LT1946A
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PI FU CTIO S
VC (Pin 1): Error Amplifier Output Pin. Tie external com-
pensation network to this pin or use the internal compen-
sation network by shorting the VC pin to the COMP pin.
External compensation consists of placing a resistor and
capacitor in series from VC to GND. Typical capacitor
rangeisfrom90pFto270pF.Typicalresistorrangeisfrom
25k to 120k.
SW (Pin 5): Switch Pin. This is the collector of the internal
NPN power switch. Minimize the metal trace area con-
nected to this pin to minimize EMI.
VIN (Pin 6): Input Supply Pin. Must be locally bypassed.
COMP (Pin 7): Internal Compensation Pin. Provides an
internal compensation network. Tie directly to the VC pin
for internal compensation. Tie to GND if not used.
FB (Pin 2): Feedback Pin. Reference voltage is 1.25V.
Connect resistive divider tap here. Minimize trace area at
FB. Set VOUT according to VOUT = 1.25 • (1+R1/R2).
SS (Pin 8): Soft-Start Pin. Place a soft-start capacitor
here. Upon start-up, 4µA of current charges the capacitor
to 1.5V. Use a larger capacitor for slower start-up. Leave
floating if not in use.
SHDN(Pin3):ShutdownPin.Tieto2.4Vormoretoenable
device. Ground to shut down. Do not float this pin.
GND (Pin 4, Exposed Pad): Ground. Tie both Pin 4 and
the exposed pad directly to local ground plane. The
ground metal to the exposed pad should be wide for better
heat dissipation. Multiple vias (local ground plane ↔
ground backplane) placed close to the exposed pad can
further aid in reducing thermal resistance.
sn1946a 1946afs
4
LT1946A
W
BLOCK DIAGRA
SS
8
V
COMP
7
C
1
4µA
120k
90pF
5
SW
COMPARATOR
A2
–
+
DRIVER
R
Q
Q1
S
1.25V
6
+
–
V
IN
+
–
REFERENCE
A1
A3
0.01Ω
Σ
V
OUT
RAMP
GENERATOR
R1 (EXTERNAL)
FB
+
–
4
GND
0.5V
R2 (EXTERNAL)
÷ 3
2.7MHz
OSCILLATOR
EXPOSED
PAD
SHDN
3
2
SHUTDOWN
1946A F02
FB
Figure 2. Block Diagram
sn1946a 1946afs
5
LT1946A
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OPERATIO
a nominal value of 0.5V. This is accomplished via com-
parator A3. This feature reduces the minimum duty cycle
thatthepartcanachievethusallowingbettercontrolofthe
switch current during start-up. When the FB pin voltage
goes above 0.5V, the oscillator returns to the normal
frequencyof2.7MHz.Asoft-startfunctionisalsoprovided
by the LT1946A. When the part is brought out of shut-
down, 4µA of current is sourced out of the SS pin. By
connecting an external capacitor to the SS pin, the rate of
voltage rise on the pin can be set. Typical values for the
soft-start capacitor range from 10nF to 200nF. The SS pin
directly limits the rate of rise on the VC pin, which in turn
limits the peak switch current. Current limit is not shown
inFigure2.Theswitchcurrentisconstantlymonitoredand
not allowed to exceed the nominal value of 2.1A. If the
switch current reaches 2.1A, the SR latch is reset regard-
less of the output of comparator A2. This current limit
protects the power switch as well as various external
components connected to the LT1946A.
The LT1946A uses a constant frequency, current mode
control scheme to provide excellent line and load regula-
tion. Please refer to Figure 2 for the following description
of the part’s operation. At the start of the oscillator cycle,
the SR latch is set, turning on the power switch Q1. The
switch current flows through the internal current sense
resistor generating a voltage. This voltage is added to a
stabilizing ramp and the resulting sum is fed into the
positive terminal of the PWM comparator A2. When this
voltageexceedsthelevelatthenegativeinputofA2,theSR
latch is reset, turning off the power switch. The level at the
negative input of A2 (VC pin) is set by the error amplifier
(A1) and is simply an amplified version of the difference
between the feedback voltage and the reference voltage of
1.250V. In this manner, the error amplifier sets the correct
peak current level to keep the output in regulation.
Two functions are provided to enable a very clean start-up
for the LT1946A. Frequency foldback is used to reduce the
oscillator frequency by one-third when the FB pin is below
W U U
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APPLICATIO S I FOR ATIO
Inductor Selection
Table 1. Recommended Inductors - LT1946A
MAX
DCR
(µH) (mΩ)
Size
LxWxH
(mm)
L
Several inductors that work well with the LT1946A are
listed in Table 1. This table is not complete, and there are
many other manufacturers and devices that can be used.
Consult each manufacturer for more detailed information
and for their entire selection of related parts, as many
differentsizesandshapesareavailable.Ferritecoreinduc-
tors should be used to obtain the best efficiency, as core
losses at 2.7MHz are much lower for ferrite cores than for
the cheaper powdered-iron ones. Choose an inductor that
can handle at least 1.5A without saturating, and ensure
that the inductor has a low DCR (copper-wire resistance)
to minimize I2R power losses. A 1.5µH to 4.7µH inductor
will be the best choice for most LT1946A designs. Note
that in some applications, the current handling require-
ments of the inductor can be lower, such as in the SEPIC
topology where each inductor only carries one-half of the
total switch current.
PART
VENDOR
RLF5018-1R5M2R1
RLF5018-2R7M1R8
RLF5018-4R7M1R4
RLF5018-100MR94
1.5
2.7
4.7
25
33
45
67
5.2x5.6x1.8 TDK
(847) 803-6100
www.tdk.com
10.0
LPO1704-122MC
LPO1704-222MC
1.2
2.2
80
120
5.5x6.6x1.0 Coilcraft
(800) 322-2645
www.coilcraft.com
CR43-2R2
CR43-3R3
2.2
3.3
71
86
4.5x4.0x3.2 Sumida
(847) 956-0666
www.sumida.com
Capacitor Selection
Low ESR (equivalent series resistance) capacitors should
beusedattheoutputtominimizetheoutputripplevoltage.
Multilayer ceramic capacitors are an excellent choice, as
they have an extremely low ESR and are available in very
small packages. X5R dielectrics are preferred, followed by
X7R, as these materials retain the capacitance over wide
TheinductorsshowninTable1werechosenforsmallsize.
For better efficiency, use similar valued inductors with a
larger volume.
voltage and temperature ranges. A 2.2µF to 20µF output
sn1946a 1946afs
6
LT1946A
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APPLICATIO S I FOR ATIO
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capacitor is sufficient for most applications, but systems
with very low output currents may need only a 1µF or
smaller output capacitor. Solid tantalum or OSCON ca-
pacitorscanbeused,buttheywilloccupymoreboardarea
than a ceramic and will have a higher ESR. Always use a
capacitor with a sufficient voltage rating.
V
OUT
200mV/DIV
AC COUPLED
I
L1
Ceramic capacitors also make a good choice for the input
decoupling capacitor, which should be placed as close as
possible to the LT1946A. A 2.2µF to 4.7µF input capacitor
is sufficient for most applications. Table 2 shows a list of
several ceramic capacitor manufacturers. Consult the
manufacturers for detailed information on their entire
selection of ceramic parts.
0.5A/DIV
1946A F03a
R
= 2.5k
C
50µs/DIV
Figure 3a. Transient Response Shows Excessive Ringing
Table 2. Ceramic Capacitor Manufacturers
V
OUT
200mV/DIV
Taiyo Yuden
AVX
(408) 573-4150
(803) 448-9411
(714) 852-2001
www.t-yuden.com
www.avxcorp.com
www.murata.com
AC COUPLED
Murata
I
L1
0.5A/DIV
Compensation
1946A F03b
TocompensatethefeedbackloopoftheLT1946A, aseries
resistor-capacitor network should be connected from the
COMPpintoGND.Formostapplications,acapacitorinthe
range of 90pF to 470pF will suffice. A good starting value
for the compensation capacitor, CC, is 270pF. The com-
pensation resistor, RC, is usually in the range of 20k to
100k. A good technique to compensate a new application
is to use a 100k potentiometer in place of RC, and use a
270pF capacitor for CC. By adjusting the potentiometer
while observing the transient response, the optimum
value for RC can be found. Figures 3a-3c illustrate this
process for the circuit of Figure 1. Figure 3a shows the
transient response with RC equal to 2.5k. The phase
marginispoorasevidencedbytheexcessiveringinginthe
output voltage and inductor current. In Figure 3b the value
of RC is increased to 6.5k, which results in a more damped
response. Figure 3c shows the results when RC is in-
creased further to 27.4k. The transient response is nicely
damped and the compensation procedure is complete.
The COMP pin provides access to an internal resistor
(120k) and capacitor (90pF). For some applications, these
values will suffice and no external RC and CC will be
needed.
R
= 6.5k
C
50µs/DIV
Figure 3b. Transient Response is Better
V
OUT
200mV/DIV
AC COUPLED
I
L1
0.5A/DIV
1946A F03c
R
= 27.4k
C
50µs/DIV
Figure 3c. Transient Response is Well Damped
Compensation-Theory
Like all other current mode switching regulators, the
LT1946A needs to be compensated for stable and efficient
operation. Two feedback loops are used in the LT1946A:
a fast current loop which does not require compensation,
and a slower voltage loop which does. Standard bode plot
analysis can be used to understand and adjust the voltage
feedback loop.
sn1946a 1946afs
7
LT1946A
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APPLICATIO S I FOR ATIO
1
As with any feedback loop, identifying the gain and phase
contribution of the various elements in the loop is critical.
Figure 4 shows the key equivalent elements of a boost
converter. Because of the fast current control loop, the
power stage of the IC, inductor, and diode have been
replaced by the equivalent transconductance amplifier
Z2 =
ESR Zero:
RHP Zero:
2• π •ESR•COUT
V
IN
2 •RL
2• π •VOUT2 •L
Z3 =
GMP. GMP acts as a current source where the output
current is proportional to the VC voltage. Note that the
maximumoutputcurrentofGMP isfiniteduetothecurrent
limit in the IC.
FS
3
P >
3
High Frequency Pole:
From Figure 4, the DC gain, poles and zeroes can be
calculated as follows:
Using the circuit of Figure 1 as an example, Table 3 shows
the parameters used to generate the bode plot shown in
Figure 5.
2
Table 3. Bode Plot Parameters
P =
1
Output Pole:
2• π •RL •COUT
Parameter
Value
28
Units
Ω
Comment
R
L
Application Specific
Application Specific
Not Adjustable
Adjustable
1
C
2.2
10
µF
OUT
P =
Error Amp Pole:
Error Amp Zero:
2
R
MΩ
pF
2• π •RO •CC
O
C
C
270
27.4
12
R
C
kΩ
Adjustable
1
Z1 =
V
V
V
Application Specific
Application Specific
Not Adjustable
Not Adjustable
Application Specific
Not Adjustable
Not Adjustable
OUT
IN
2• π •RC •CC
5
V
G
MA
G
MP
L
40
µmho
mho
µH
1.25
VOUT
A =
•GMA •RO •GMP •RL
5
DC Gain:
2.2
2.7
10
F
MHz
mΩ
S
ESR
–
+
G
V
MP
OUT
From Figure 5, the phase when the gain reaches 0dB is
122° giving a phase margin of 58°. This is more than
adequate. The cross-over frequency is 90kHz, which is
about 30 times lower than the frequency of the right half
planezeroZ2.Itisimportantthatthecross-overfrequency
beatleast3timeslowerthanthefrequencyoftheRHPzero
to achieve adequate phase margin.
ESR
R
L
C
+
OUT
1.250V
REFERENCE
V
C
R
R
1
2
G
MA
–
R
C
R
O
C
C
G
G
OUT
: TRANSCONDUCTANCE AMPLIFIER INSIDE IC
MA
MP
: POWER STAGE TRANSCONDUCTANCE AMPLIFIER
C
: OUTPUT CAPACITOR
R : OUTPUT RESISTANCE DEFINED AS V
DIVIDED BY I
(MAX)
LOAD
L
OUT
R1, R2: FEEDBACK RESISTOR DIVIDER NETWORK
R : OUTPUT RESISTANCE OF G
O
MA
R : COMPENSATION RESISTOR
C
C : COMPENSATION CAPACITOR
C
Figure 4. Boost Converter Equivalent Model
sn1946a 1946afs
8
LT1946A
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APPLICATIO S I FOR ATIO
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100
Setting Output Voltage
To set the output voltage, select the values of R1 and R2
(see Figure 1) according to the following equation:
50
VOUT
1.25V
R1= R2
– 1
0
A good range for R2 is from 5k to 30k.
–50
Layout Hints
100
1k
10k
100k
1M
FREQUENCY (Hz)
ThehighspeedoperationoftheLT1946Ademandscareful
attention to board layout. You will not get advertised
performance with careless layouts. Figure 6 shows the
recommended component placement for a boost con-
verter.
1946A FO5a
0
–100
GROUND PLANE
CSS
C1
58°
+
C
C
C
V
IN
R
–180
–200
1
2
3
4
8
7
6
5
R1
100
1k
10k
100k
1M
FREQUENCY (Hz)
L1
LT1946A
1946A FO5b
R2
SHUTDOWN
Figure 5. Gain and Phase Plots of Figure 1 Circuit
MULTIPLE
VIAs
Diode Selection
C2
GND
ASchottkydiodeisrecommendedforusewiththeLT1946A.
The Microsemi UPS120 is a very good choice. Where the
input to output voltage differential exceeds 20V, use the
UPS140(a40Vdiode).Thesediodesareratedtohandlean
average forward current of 1A. For applications where the
average forward current of the diode is less than 0.5A, an
ON Semiconductor MBR0520 diode can be used.
V
OUT
19949 F04
NOTE: DIRECT HIGH CURRENT PATHS USING WIDE PC TRACES. MINIMIZE TRACE AREA AT
PIN 1(VC) AND PIN 2(FB). USE MULTIPLE VIAS TO TIE PIN 4 COPPER TO GROUND PLANE. USE
VIAS AT ONE LOCATION ONLY TO AVOID INTRODUCING SWITCHING CURRENTS INTO THE
GROUND PLANE.
Figure 6. Recommended Component
Placement for Boost Converter
sn1946a 1946afs
9
LT1946A
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TYPICAL APPLICATIO S
Low Profile (<1.1mm Tall) Triple Output TFT Supply (10V, –10V, 20V)
D2
D3
V
ON
20V
5mA
C5
0.1µF
L1
1.5µH
D1
A
VDD
V
IN
10V
5V
475mA
6
5
R1
75k
V
SW
IN
3
8
7
OFF ON
SHDN
2
SS LT1946A FB
COMP
+
C2
20µF
C3
1µF
C1
4.7µF
V
GND*
4
C
1
R2
10.5k
C
SS
R
59k
C
C
100nF
C
150pF
C6
0.1µF
C1–C6: X5R or X7R
C1: 4.7µF, 6.3V
C2: 2× 10µF, 10V
C3: 1µF, 25V
D4
D5
C4
2.2µF
C4: 2.2µF, 10V
C5–C6: 0.1µF, 10V
V
OFF
D1: MICROSEMI UPS120 OR EQUIVALENT
D2–D5: ZETEX BAT54S OR EQUIVALENT
L1: COILCRAFT LP01704-152MC
–10V
10mA
1946A TA02
* EXPOSED PAD MUST ALSO BE GROUNDED
Transient Response
Efficiency
90
85
80
75
70
65
60
55
50
AVDD
50mV/DIV
AC COUPLED
ILI
0.5A/DIV
V
V
LOAD = 5mA
LOAD = 10mA
ON
OFF
350mA
200mA
AVDD LOAD
0
100
200
300
400
500
A
VDD
LOAD CURRENT (mA)
100µs/DIV
1946A TA03
1946A TA04
sn1946a 1946afs
10
LT1946A
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TYPICAL APPLICATIO S
Triple Output TFT Supply Uses SEPIC Topology for Output Disconnect
D2
V
ON
23V
C4
10mA
0.22µF
D3
V
OFF
–12V
C5
0.22µF
10mA
L1
10µH
D1
A
VDD
V
IN
12V
12V ± 10%
250mA
6
5
SW
C3
1µF
L2
10µH
R1
V
IN
3
8
1
84.5k
OFF ON
SHDN
SS LT1946A FB
2
+
C2
C1
V
C
20µF
2.2µF
COMP
7
GND*
4
R2
9.76k
C
SS
100nF
D1: MICROSEMI UPS120 OR EQUIVALENT
D2–D3: CENTRAL SEMI CMDSH-3
L1–L2: TDK RLF5018-100MR94
C1–C5: X5R or X7R
C1: 2.2µF, 6.3V
C2: 2× 10µF, 16V
C3: 1µF, 25V
1946A TA09
* EXPOSED PAD MUST ALSO BE GROUNDED
C4: 0.22µF, 25V
C5: 0.22µF, 16V
MS8E Package
8-Lead Plastic MSOP
(Reference LTC DWG # 05-08-1662)
BOTTOM VIEW OF
EXPOSED PAD OPTION
2.06 ± 0.102
3.00 ± 0.102
(.118 ± .004)
(NOTE 3)
0.889 ± 0.127
(.035 ± .005)
2.794 ± 0.102
(.110 ± .004)
0.52
(.206)
REF
(.080 ± .004)
1
8
7 6
5
1.83 ± 0.102
(.072 ± .004)
5.23
(.206)
MIN
3.2 – 3.45
(.126 – .136)
3.00 ± 0.102
(.118 ± .004)
NOTE 4
2.083 ± 0.102
(.082 ± .004)
4.88 ± 0.1
(.192 ± .004)
DETAIL “A”
0.254
(.010)
0° – 6° TYP
GAUGE PLANE
0.65
(.0256)
BSC
0.42 ± 0.04
1
2
3
4
(.0165 ± .0015)
8
TYP
0.53 ± 0.015
(.021 ± .006)
1.10
(.043)
MAX
0.86
(.34)
REF
RECOMMENDED SOLDER PAD LAYOUT
DETAIL “A”
0.18
(.077)
SEATING
PLANE
NOTE:
0.22 – 0.38
(.009 – .015)
1. DIMENSIONS IN MILLIMETER/(INCH)
2. DRAWING NOT TO SCALE
0.13 ± 0.05
(.005 ± .002)
0.65
(.0256)
BCS
3. DIMENSION DOES NOT INCLUDE MOLD FLASH, PROTRUSIONS OR GATE BURRS.
MOLD FLASH, PROTRUSIONS OR GATE BURRS SHALL NOT EXCEED 0.152mm (.006") PER SIDE
4. DIMENSION DOES NOT INCLUDE INTERLEAD FLASH OR PROTRUSIONS.
MSOP (MS8E) 1001
INTERLEAD FLASH OR PROTRUSIONS SHALL NOT EXCEED 0.152mm (.006") PER SIDE
5. LEAD COPLANARITY (BOTTOM OF LEADS AFTER FORMING) SHALL BE 0.102mm (.004") MAX
sn1946a 1946afs
Information furnished by Linear Technology Corporation is believed to be accurate and reliable.
However, no responsibility is assumed for its use. Linear Technology Corporation makes no represen-
tationthattheinterconnectionofitscircuitsasdescribedhereinwillnotinfringeonexistingpatentrights.
11
LT1946A
U
TYPICAL APPLICATIO S
Low Profile (<1.1mm Tall) Triple Output TFT Supply (8V, –8V, 24V)
D2
D3
D4
D5
V
ON
23V
5mA
C5
0.1µF
C6
0.1µF
C7
0.1µF
Efficiency
L1
90
85
80
75
70
65
60
55
50
D1
1.2µH
AV
8V
DD
V
IN
3.3V
375mA
6
5
R2
V
SW
IN
3
8
7
28.7k
OFF ON
SHDN
2
SS LT1946A FB
COMP
+
C2
C4
1µF
C1
20µF
4.7µF
V
GND*
4
C
1
R3
5.23k
C
SS
100nF
V
V
LOAD = 5mA
ON
OFF
LOAD = 10mA
C8
0.1µF
C1–C8: X5R or X7R
C1: 4.7µF, 6.3V
C2: 2× 10µF, 10V
C3: 2.2µF, 10V
C4: 1µF, 25V
D7
D6
0
100
200
300
400
C3
2.2µF
A
LOAD CURRENT (mA)
VDD
1946A TA06
C5, C6, C8: 0.1µF, 10V
C7: 0.1µF, 16V
V
OFF
–8V
D1: MICROSEMI UPS120 OR EQUIVALENT
D2–D7: ZETEX BAT54S OR EQUIVALENT
L1: COILCRAFT LP01704-122MC
10mA
1946A TA05
* EXPOSED PAD MUST ALSO BE GROUNDED
Transient Response
Start-Up Waveforms
AVDD
5V/DIV
AVDD
50mV/DIV
AC COUPLED
VON
10V/DIV
ILI
0.5A/DIV
VOFF
5V/DIV
350mA
ILOAD
200mA
IIN
0.5A/DIV
1946A TA07
1946A TA08
1ms/DIV
50µs/DIV
RELATED PARTS
PART NUMBER
LT1613
DESCRIPTION
550mA (I ), 1.4MHz, Step-Up DC/DC Converter
COMMENTS
V
V
= 0.9V to 10V, V
to 34V, I = 3mA, I < 1µA, ThinSOTTM
OUT Q SD
SW
IN
IN
LT1615/LT1615-1
300mA/0.75mA (I ), Constant Off-Time Step-Up
= 1V to 15V, V
to 34V, I = 20µA, I < 1µA, ThinSOT
OUT Q SD
SW
DC/DC Converter
LT1930/LT1930A
LT1946
1A (I ), 1.2MHz/2.2MHz, Step-Up DC/DC Converter
V
V
V
= 2.6V to 16V, V
to 34V, I = 4.2mA/5.5mA, I < 1µA, ThinSOT
OUT Q SD
SW
IN
IN
IN
1.5A (I ), 1.2MHz, Step-Up DC/DC Converter
= 2.45V to 16V, V
to 34V, I = 3.2mA, I < 1µA, MS8
OUT Q SD
SW
LT1961
1.5A (I ), 1.25MHz, Step-Up DC/DC Converter
= 3V to 25V, V
to 35V, I = 0.9mA, I < 6µA, MS8E
SW
OUT Q SD
ThinSOT is a trademark of Linear Technology Corporation.
sn1946a 1946afs
LT/TP 1102 2K • PRINTED IN USA
12 LinearTechnology Corporation
1630 McCarthy Blvd., Milpitas, CA 95035-7417
●
●
(408) 432-1900 FAX: (408) 434-0507 www.linear.com
LINEAR TECHNOLOGY CORPORATION 2001
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