MCP47A1 [MICROCHIP]
6-Bit Volatile DAC with Command Code;型号: | MCP47A1 |
厂家: | MICROCHIP |
描述: | 6-Bit Volatile DAC with Command Code |
文件: | 总70页 (文件大小:1836K) |
中文: | 中文翻译 | 下载: | 下载PDF数据表文档文件 |
MCP47A1
6-Bit Volatile DAC with Command Code
Package Types
Features:
MCP47A1
• 6-Bit DAC
- 65 Taps: 64 Resistors with Taps to Full-Scale
and Zero-Scale (Wiper Code 00h to 40h)
VDD
VSS
SCL
A
VREF
VOUT
SDA
1
2
3
6
5
4
W
B
• VREF Pull-down Resistance: 20 k (typical)
• VOUT Voltage Range
SC70-6
- VSS to VREF
™
• I2C Protocol
Device Block Diagram
- Supports SMBus 2.0 Write Byte/Word
Protocol Formats
- Supports SMBus 2.0 Read Byte/Word
Protocol Formats
VDD
VREF
A
Power-up
and
Brown-out
Control
- Slave Addresses: 5Ch and 7Ch
VSS
• Brown-out Reset Protection (1.5V typical)
• Power-on Default Wiper Setting (Mid-scale)
• Low-PowerOperation:90 µAStaticCurrent(typical)
• Wide Operating Voltage Range:
2-Wire
Interface
and
Control
Logic
SDA
SCL
- 1.8V to 5.5V
VOUT
• Low Tempco: 15 ppm (typical)
• 100 kHz (typical) Bandwidth (-3 dB) Operation
• Extended Temperature Range (-40°C to +125°C)
• Small Packages, SC70-6
B
• Lead Free (Pb-free) Package
Description
Applications
The MCP47A1 devices are volatile, 6-Bit digital
potentiometers with a buffered output. The wiper
setting is controlled through an I2C serial interface. The
I2C slave addresses of “010 1110”and “011 1110”
are supported.
• Set point or offset trimming
• Cost-sensitive mechanical trim pot replacement
2012 Microchip Technology Inc.
DS25154A-page 1
MCP47A1
Device Features
Device
Package(s)
(1)
MCP47A1
MCP47DA1
MCP4706
MCP4716
MCP4726
MCP4725
I2C 65
I2C 65
64
64
20
30
00h - 40h
00h - 7Fh
00h - FFh
20h 5Ch, 7Ch 1.8V
V
SS to VREF
SC70-6
to 5.5V
(2)
(1)
40h 5Ch, 7Ch 1.8V
1/3 VREF to
2/3 VREF
SC70-6,
SOT-23-6
to 5.5V
(3)
(3)
(3)
(4)
I2C 256 256
I2C 1024 1024
I2C 4096 4096
210
210
210
7Fh
Cxh
2.7V to VSS to VDD or SOT-23-6,
5.5V
(5)
VSS to VREF
DFN-6(2x2)
000h - 3FFh 1FFh Cxh
000h - FFFh 3FFh Cxh
2.7V to VSS to VDD or SOT-23-6,
5.5V
(5)
VSS to VREF
DFN-6(2x2)
2.7V to VSS to VDD or SOT-23-6,
5.5V
(5)
VSS to VREF
VSS to VDD
DFN-6(2x2)
SOT-23-6
I2C 4096 4096 N.A. 000h - FFFh 3FFh Cxh
2.7V to
5.5V
Note 1: Analog characteristics only tested from 2.7V to 5.5V.
2: Refer to MCP47DA1 Data Sheet (DS25118).
3: The A2:A0 bits are determined by device ordered.
4: The A2 and A1 bits are determined by device ordered and A0 is determined by the state of the A0 pin.
5: User programmable.
DS25154A-page 2
2012 Microchip Technology Inc.
MCP47A1
1.0
ELECTRICAL CHARACTERISTICS
Absolute Maximum Ratings †
Voltage on VDD with respect to VSS .......................................................................................................... 0.6V to +7.0V
Voltage on SCL, and SDA with respect to VSS ..................................................................................................... -0.6V to VDD + 0.3V
Voltage on all other pins (VOUT and VREF) with respect to VSS ..................................................................... -0.3V to VDD + 0.3V
Input clamp current, IIK (VI < 0, VI > VDD)............................................................................................................ ±20 mA
Output clamp current, IOK (VO < 0 or VO > VDD).................................................................................................. ±20 mA
Maximum output current sunk by any Output pin .................................................................................................. 25 mA
Maximum output current sourced by any Output pin ............................................................................................ 25 mA
Maximum current out of VSS pin .......................................................................................................................... 100 mA
Maximum current into VDD pin ............................................................................................................................. 100 mA
Maximum current into VREF pin............................................................................................................................. 250 uA
Maximum current sourced by VOUT pin ................................................................................................................. 40 mA
Maximum current sunk by VREF pin....................................................................................................................... 40 mA
Package power dissipation (TA = +50°C, TJ = +150°C)
SC70-6..................................................................................................................................................... 480 mW
Storage temperature .............................................................................................................................. -65°C to +150°C
Ambient temperature with power applied .............................................................................................. -40°C to +125°C
ESD protection on all pins .......................................................................................................................... 6 kV (HBM)
..................................................................................................................................................................... 400V (MM)
1.5 kV (CDM)
Latchup (JEDEC JESD78A) at +125°C ............................................................................................................. ±100 mA
Soldering temperature of leads (10 seconds)...................................................................................................... +300°C
Maximum Junction Temperature (TJ) .................................................................................................................. +150°C
† Notice: Stresses above those listed under “Maximum Ratings” may cause permanent damage to the device. This is
a stress rating only and functional operation of the device at those or any other conditions above those indicated in the
operational listings of this specification is not implied. Exposure to maximum rating conditions for extended periods may
affect device reliability.
2012 Microchip Technology Inc.
DS25154A-page 3
MCP47A1
AC/DC CHARACTERISTICS
Standard Operating Conditions (unless otherwise specified)
Operating Temperature
–40°C TA +125°C (extended)
DC Characteristics
All parameters apply across the specified operating ranges unless noted.
VDD = +2.7V to +5.5V. CL = 1 nF, RL = 5 k .
Typical specifications represent values for VDD = 5.5V, TA = +25°C.
Parameters
Sym
Min
Typ
Max
Units
Conditions
Supply Voltage
VDD
2.7
1.8
—
—
—
—
5.5
5.5
V
V
V
Analog Characteristics specified
Digital Characteristics specified
RAM retention voltage (VRAM) < VBOR
VDD Start Voltage
to ensure Wiper to
default reset state
VBOR
VDDRR
TBORD
1.65
VDD Rise Rate to
ensure Power-on
Reset
Note 5
V/ms
µS
Delay after device
exits the reset
state
—
—
1
(VDD > VBOR) to
Digital Interface
Active
Delay after device
exits the reset
state
(VDD > VBOR) to
VOUT valid
TOUTV
20
µS
µA
Within ± 0.5 LSb of VREF / 2
(for default POR/BOR wiper value).
Supply Current
(Note 6)
IDD
—
130
220
Serial Interface Active,
Write all 0’s to Volatile Wiper,
No Load on VOUT
VDD = 5.5V, VREF = VDD
,
F
SCL = 400 kHz
—
1
90
—
130
VDD
µA
V
Serial Interface Inactive (Static),
(Stop condition, SCL = SDA = VIH),
No Load on VOUT
Wiper = 0, VDD = 5.5V, VREF = VDD
VREF Input Range
VREF
Note 7
Note 1: Resistance is defined as the resistance between the VREF pin and the VSS pin.
2: INL and DNL are measured at VOUT from Code = 00h (Zero-Scale) through Code = 3Fh (Full-Scale - 1).
3: This specification by design.
4: Nonlinearity is affected by wiper resistance (RW), which changes significantly over voltage and
temperature.
5: POR/BOR is not rate dependent.
6: Supply current is independent of VREF current.
7: See Section 7.1.3.
DS25154A-page 4
2012 Microchip Technology Inc.
MCP47A1
AC/DC CHARACTERISTICS (CONTINUED)
Standard Operating Conditions (unless otherwise specified)
Operating Temperature –40°C TA +125°C (extended)
DC Characteristics
All parameters apply across the specified operating ranges unless noted.
VDD = +2.7V to +5.5V. CL = 1 nF, RL = 5 k .
Typical specifications represent values for VDD = 5.5V, TA = +25°C.
Parameters
Sym
Min
Typ
Max
Units
Conditions
Output Amplifier
Minimum Output
Voltage
VOUT(MIN)
VOUT(MAX)
—
—
VSS
—
—
V
V
Device Output minimum drive
Device Output maximum drive
Maximum Output
Voltage
VREF
Phase Margin
Slew Rate
PM
SR
ISC
—
—
5
66
0.55
15
—
—
24
Degree (°) CL = 400 pF, RL =
V/µs
mA
Short Circuit
Current
Settling Time
tSETTLING
—
15
—
µs
External Reference (VREF) (Note 3)
Input Capacitance
CVREF
THD
—
—
7
—
—
pF
Total Harmonic
Distortion
-73
dB
VREF = 1.65V ± 0.1V,
Frequency = 1 kHz
Dynamic Performance (Note 3)
Major Code
Transition Glitch
—
—
45
—
—
nV-s
nV-s
1 LSb change around major carry
(20h to 1Fh)
Digital
<10
Feedthrough
Note 1: Resistance is defined as the resistance between the VREF pin and the VSS pin.
2: INL and DNL are measured at VOUT from Code = 00h (Zero-Scale) through Code = 3Fh (Full-Scale - 1).
3: This specification by design.
4: Nonlinearity is affected by wiper resistance (RW), which changes significantly over voltage and
temperature.
5: POR/BOR is not rate dependent.
6: Supply current is independent of VREF current.
7: See Section 7.1.3.
2012 Microchip Technology Inc.
DS25154A-page 5
MCP47A1
AC/DC CHARACTERISTICS (CONTINUED)
Standard Operating Conditions (unless otherwise specified)
Operating Temperature –40°C TA +125°C (extended)
DC Characteristics
Parameters
All parameters apply across the specified operating ranges unless noted.
VDD = +2.7V to +5.5V. CL = 1 nF, RL = 5 k .
Typical specifications represent values for VDD = 5.5V, TA = +25°C.
Sym
Min
Typ
Max
Units
Conditions
Resistance
(± 20%)
RVREF
16.0
20
24.0
k
Note 1,
Resolution
N
RS
65
RVREF / 64
50
Taps
No Missing Codes
Note 3
Step Resistance
—
—
—
—
—
—
—
—
—
—
Nominal
Resistance
Tempco
RVREF/T
ppm/°C
ppm/°C
ppm/°C
ppm/°C
TA = -20°C to +70°C
TA = -40°C to +85°C
TA = -40°C to +125°C
Code = Midscale (20h)
100
150
Ratiometeric
Tempco
VOUT/T
15
V
OUT Accuracy
OUT Load
0.72
5
0.75
—
0.78
—
V
VREF = 1.5V, code = 20h
Resistive Load
V
LVOUTR
LVOUTC
IVREF
k
nF
µA
—
—
1
Capacitive Load
VREF = 5.5V
Maximum current
through Terminal
(VREF) Note 3
—
—
345
Leakage current
into VREF
IL
—
-1
100
±0.35
±0.35
±0.25
±0.25
100
—
+1
nA
LSb
LSb
LSb
LSb
kHz
pF
VREF = VSS
Full-Scale Error
(code = 40h)
VFSE
VZSE
INL
VREF = VDD
Zero-Scale Error
(code = 00h)
-0.75
-1
+0.75
+1
VREF = VDD
VOUT Integral
Nonlinearity
Note 2, VREF = VDD
Note 2, VREF = VDD
VOUT Differential
DNL
BW
-0.5
—
+0.5
—
Nonlinearity
Bandwidth -3 dB
VDD = 5.0V, VREF = 3.0V ± 2.0V,
Code = 20h
Capacitance
CREF
—
75
—
f =1 MHz, Code = Full-Scale
(VREF
)
Note 1: Resistance is defined as the resistance between the VREF pin and the VSS pin.
2: INL and DNL are measured at VOUT from Code = 00h (Zero-Scale) through Code = 3Fh (Full-Scale - 1).
3: This specification by design.
4: Nonlinearity is affected by wiper resistance (RW), which changes significantly over voltage and
temperature.
5: POR/BOR is not rate dependent.
6: Supply current is independent of VREF current.
7: See Section 7.1.3.
DS25154A-page 6
2012 Microchip Technology Inc.
MCP47A1
AC/DC CHARACTERISTICS (CONTINUED)
Standard Operating Conditions (unless otherwise specified)
Operating Temperature –40°C TA +125°C (extended)
DC Characteristics
All parameters apply across the specified operating ranges unless noted.
VDD = +2.7V to +5.5V. CL = 1 nF, RL = 5 k .
Typical specifications represent values for VDD = 5.5V, TA = +25°C.
Parameters
Sym
Min
Typ
Max
Units
Conditions
Digital Inputs/Outputs (SDA, SCK)
Schmitt Trigger
High Input
VIH
0.7 VD
—
—
V
1.8V VDD 5.5V
D
Threshold
Schmitt Trigger
Low Input
VIL
-0.5
—
0.3VD
V
1.8V VDD 5.5V
D
Threshold
Hysteresis of
Schmitt Trigger
Inputs (Note 3)
VHYS
N.A.
N.A.
—
—
—
—
—
—
V
V
V
V
DD < 2.0V
VDD 2.0V
VDD < 2.0V
100 kHz
400 kHz
SDA
and
SCL
0.1 VD
D
0.05 V
DD
—
—
V
VDD 2.0V
Output Low
Voltage (SDA)
VOL
VSS
—
—
0.4
V
V
VDD 2.0V, IOL = 3 mA
VDD < 2.0V, IOL = 1 mA
VSS
0.2VD
D
Input Leakage
Current
IIL
-1
—
1
µA
pF
VREF = VDD and VREF = VSS
fC = 400 kHz
Pin Capacitance
RAM (Wiper) Value
Value Range
CIN, COUT
—
10
—
N
0h
—
40h
hex
hex
Wiper POR/BOR
Value
NPOR/BOR
20h
Power Requirements
Power Supply
Sensitivity
PSS
—
0.0015
0.003
5
%/%
VREF = VDD, Code = 20h
Note 1: Resistance is defined as the resistance between the VREF pin and the VSS pin.
2: INL and DNL are measured at VOUT from Code = 00h (Zero-Scale) through Code = 3Fh (Full-Scale - 1).
3: This specification by design.
4: Nonlinearity is affected by wiper resistance (RW), which changes significantly over voltage and
temperature.
5: POR/BOR is not rate dependent.
6: Supply current is independent of VREF current.
7: See Section 7.1.3.
2012 Microchip Technology Inc.
DS25154A-page 7
MCP47A1
2
1.1
I C Mode Timing Waveforms and Requirements
SCL
93
91
90
92
SDA
START
STOP
Condition
Condition
FIGURE 1-1:
I2C Bus Start/Stop Bits Timing Waveforms.
103
102
92
100
101
109
SCL
90
106
91
107
SDA
In
110
109
SDA
Out
Note:
Refer to specification D102 (Cb) for load conditions.
I2C Bus Data Timing.
FIGURE 1-2:
TABLE 1-1:
I2C BUS START/STOP BITS REQUIREMENTS
I2C AC Characteristics
Standard Operating Conditions (unless otherwise specified)
Operating Temperature –40C TA +125C (Extended)
Operating Voltage VDD range is described in Section 2.0 “Typical
Performance Curves”
Param.
Symbol
No.
Characteristic
Standard Mode
Min
Max
Units
Conditions
FSCL
0
100
400
400
400
—
kHz Cb = 400 pF, 1.8V - 5.5V
Fast Mode
0
kHz Cb = 400 pF, 2.7V - 5.5V
D102
90
Cb
Bus capacitive
loading
100 kHz mode
400 kHz mode
100 kHz mode
400 kHz mode
100 kHz mode
400 kHz mode
100 kHz mode
400 kHz mode
100 kHz mode
400 kHz mode
—
pF
pF
—
TSU:STA START condition
Setup time
4700
600
4000
600
4000
600
4000
600
ns
ns
ns
ns
ns
ns
ns
ns
Only relevant for repeated
START condition
—
91
THD:STA START condition
Hold time
—
After this period, the first
clock pulse is generated
—
92
TSU:STO STOP condition
Setup time
—
—
93
THD:STO STOP condition
Hold time
—
—
DS25154A-page 8
2012 Microchip Technology Inc.
MCP47A1
TABLE 1-2:
I2C AC Characteristics
I2C BUS DATA REQUIREMENTS (SLAVE MODE)
Standard Operating Conditions (unless otherwise specified)
Operating Temperature –40C TA +125C (Extended)
Operating Voltage VDD range is described in AC/DC characteristics
Parame-
ter No.
Sym
Characteristic
Min
Max Units
Conditions
100
THIGH
Clockhightime 100 kHz mode
400 kHz mode
4000
—
ns
1.8V-5.5V
600
—
—
ns
ns
2.7V-5.5V
101
TLOW
Clock low time
100 kHz mode
4700
1.8V-5.5V
400 kHz mode
100 kHz mode
1300
—
—
ns
ns
2.7V-5.5V
(5)
TRSCL SCL rise time
TRSDA SDA rise time
1000
Cb is specified to be from
10 to 400 pF
102A
400 kHz mode
100 kHz mode
20 + 0.1Cb
—
300
ns
ns
(5)
1000
Cb is specified to be from
10 to 400 pF
102B
400 kHz mode
100 kHz mode
20 + 0.1Cb
—
300
300
ns
ns
(5)
TFSCL
SCL fall time
Cb is specified to be from
10 to 400 pF
103A
400 kHz mode
100 kHz mode
20 + 0.1Cb
—
40
ns
ns
(5)
TFSDA SDA fall time
300
Cb is specified to be from
10 to 400 pF
103B
(5)
400 kHz mode
300
—
ns
ns
20 + 0.1Cb
0
106
THD:DAT Data input hold 100 kHz mode
1.8V-5.5V (Note 6)
2.7V-5.5V (Note 6)
Note 5
time
400 kHz mode
0
—
—
ns
ns
ns
ns
107
109
TSU:DAT Data input
setup time
100 kHz mode
400 kHz mode
100 kHz mode
250
100
—
—
TAA
Output valid
from clock
3450
Note 5
400 kHz mode
100 kHz mode
—
900
—
ns
ns
110
TBUF
Bus free time
4700
Time the bus must be free
before a new transmission
can start
400 kHz mode
1300
—
ns
TSP
Input filter spike 100 kHz mode
—
—
50
50
ns
ns
Philips Spec states N.A.
suppression
400 kHz mode
(SDA and SCL)
Note 1: As a transmitter, the device must provide this internal minimum delay time to bridge the undefined region
(min. 300 ns) of the falling edge of SCL to avoid unintended generation of START or STOP conditions.
2: A fast-mode (400 kHz) I2C-bus device can be used in a standard-mode (100 kHz) I2C-bus system, but the
requirement tsu; DAT 250 ns must then be met. This will automatically be the case if the device does not
stretch the LOW period of the SCL signal. If such a device does stretch the LOW period of the SCL signal,
it must output the next data bit to the SDA line
TR max.+tsu;DAT = 1000 + 250 = 1250 ns (according to the standard-mode I2C bus specification) before
the SCL line is released.
3: The MCP47A1 device must provide a data hold time to bridge the undefined part between VIH and VIL of
the falling edge of the SCL signal. This specification is not a part of the I2C specification, but must be
tested in order to guarantee that the output data will meet the setup and hold specifications for the
receiving device.
4: Use Cb in pF for the calculations.
5: Not tested.
6: A Master Transmitter must provide a delay to ensure that difference between SDA and SCL fall times do
not unintentionally create a Start or Stop condition.
2012 Microchip Technology Inc.
DS25154A-page 9
MCP47A1
TEMPERATURE CHARACTERISTICS
Electrical Specifications: Unless otherwise indicated, VDD = +2.7V to +5.5V, VSS = GND.
Parameters
Temperature Ranges
Sym
Min
Typ
Max
Units
Conditions
Specified Temperature Range
Operating Temperature Range
Storage Temperature Range
Thermal Package Resistances
Thermal Resistance, 6L-SC70
TA
TA
TA
-40
-40
-65
—
—
—
+125
+125
+150
°C
°C
°C
JA
—
207
—
°C/W Note 1
Note 1: Package Power Dissipation (PDIS) is calculated as follows:
PDIS = (TJ - TA) / JA
where: TJ = Junction Temperature, TA = Ambient Temperature.
,
DS25154A-page 10
2012 Microchip Technology Inc.
MCP47A1
2.0
TYPICAL PERFORMANCE CURVES
Note 1: The graphs and tables provided following this note are a statistical summary based on a limited number
of samples and are provided for informational purposes only. The performance characteristics listed herein
are not tested or guaranteed. In some graphs or tables, the data presented may be outside the specified
operating range (e.g., outside specified power supply range) and therefore outside the warranted range.
Note: Unless otherwise indicated, TA = +25°C, VDD = VREF = 5V, VSS = 0V, RL = 5 k, CL = 1 nF.
Typical Device
Typical Device
1.00
0.75
0.50
0.25
0.00
ꢀ0.25
ꢀ0.50
ꢀ0.75
ꢀ1.00
1.00
0.75
0.50
0.25
0.00
ꢀ0.25
ꢀ0.50
ꢀ0.75
ꢀ1.00
ꢀ40Cꢁꢀ 5.5V
ꢀ40Cꢁꢀ 2.7V
ꢀ40Cꢁꢀ 1.8V
ꢀ40Cꢁꢀ 1.0V
+25Cꢁꢀ 5.5V
+25Cꢁꢀ 2.7V
+25Cꢁꢀ 1.8V
+25Cꢁꢀ 1.0V
+85Cꢁꢀ 5.5V
+85Cꢁꢀ 2.7V
+85Cꢁꢀ 1.8V
+85Cꢁꢀ 1.0V
+125Cꢁꢀ 5.5V
+125Cꢁꢀ 2.7V
+125Cꢁꢀ 1.8V
+125Cꢁꢀ 1.0V
ꢀ40Cꢁꢀ 2.0V
ꢀ40Cꢁꢀ 1.8V
ꢀ40Cꢁꢀ 1.0V
+25Cꢁꢀ 2.0V
+25Cꢁꢀ 1.8V
+25Cꢁꢀ 1.0V
+85Cꢁꢀ 2.0V
+85Cꢁꢀ 1.8V
+85Cꢁꢀ 1.0V
+125Cꢁꢀ 2.0V
+125Cꢁꢀ 1.8V
+125Cꢁꢀ 1.0V
0
8
16
24
32
40
48
56
64
0
8
16
24
32
40
48
56
64
DAC Wiper Code
DAC Wiper Code
Analog Performance Specified for VDD ≥ 2.7V.
FIGURE 2-1:
and Temperature.
INL vs. Code (00h to 3Fh)
FIGURE 2-3:
and Temperature.
INL vs. Code (00h to 3Fh)
VDD = 5.5V, VREF = 5.5V, 2.7V, 1.8V, and 1.0V.
VDD = 2.0V, VREF = 2.0V, 1.8V, and 1.0V.
Typical Device
Typical Device
1.00
1.00
0.75
0.50
0.25
0.00
ꢀ0.25
ꢀ0.50
ꢀ0.75
ꢀ1.00
0.75
0.50
0.25
0.00
ꢀ0.25
ꢀ0.50
ꢀ40Cꢁꢀ 2.7V
ꢀ40Cꢁꢀ 1.8V
ꢀ40Cꢁꢀ 1.0V
+25Cꢁꢀ 2.7V
+25Cꢁꢀ 1.8V
+25Cꢁꢀ 1.0V
+85Cꢁꢀ 2.7V
+85Cꢁꢀ 1.8V
+85Cꢁꢀ 1.0V
+125Cꢁꢀ 2.7V
+125Cꢁꢀ 1.8V
+125Cꢁꢀ 1.0V
ꢀ0.75
ꢀ1.00
ꢀ40Cꢁꢀ 1.6V
ꢀ40Cꢁꢀ 1.0V
+25Cꢁꢀ 1.6V
+25Cꢁꢀ 1.0V
+85Cꢁꢀ 1.6V
+85Cꢁꢀ 1.0V
+125Cꢁꢀ 1.6V
+125Cꢁꢀ 1.0V
0
8
16
24
32
40
48
56
64
0
8
16
24
32
40
48
56
64
DAC Wiper Code
DAC Wiper Code
Analog Performance Specified for VDD ≥ 2.7V.
FIGURE 2-2:
and Temperature.
DD = 2.7V, VREF = 2.7V, 1.8V, and 1.0V.
INL vs. Code (00h to 3Fh)
FIGURE 2-4:
and Temperature.
VDD = 1.8V, VREF = 1.6V, and 1.0V.
INL vs. Code (00h to 3Fh)
V
2012 Microchip Technology Inc.
DS25154A-page 11
MCP47A1
Note: Unless otherwise indicated, TA = +25°C, VDD = VREF = 5V, VSS = 0V, RL = 5 k, CL = 1 nF.
Typical Device
Typical Device
0.50
0.25
0.00
ꢀ0.25
ꢀ0.50
0.50
0.25
0.00
ꢀ0.25
ꢀ0.50
ꢀ40Cꢁꢀ 5.5V
ꢀ40Cꢁꢀ 2.7V
ꢀ40Cꢁꢀ 1.8V
ꢀ40Cꢁꢀ 1.0V
+25Cꢁꢀ 5.5V
+25Cꢁꢀ 2.7V
+25Cꢁꢀ 1.8V
+25Cꢁꢀ 1.0V
+85Cꢁꢀ 5.5V
+85Cꢁꢀ 2.7V
+85Cꢁꢀ 1.8V
+85Cꢁꢀ 1.0V
+125Cꢁꢀ 5.5V
+125Cꢁꢀ 2.7V
+125Cꢁꢀ 1.8V
+125Cꢁꢀ 1.0V
ꢀ40Cꢁꢀ 2.0V
ꢀ40Cꢁꢀ 1.8V
ꢀ40Cꢁꢀ 1.0V
+25Cꢁꢀ 2.0V
+25Cꢁꢀ 1.8V
+25Cꢁꢀ 1.0V
+85Cꢁꢀ 2.0V
+85Cꢁꢀ 1.8V
+85Cꢁꢀ 1.0V
+125Cꢁꢀ 2.0V
+125Cꢁꢀ 1.8V
+125Cꢁꢀ 1.0V
0
8
16
24
32
40
48
56
64
0
8
16
24
32
40
48
56
64
DAC Wiper Code
DAC Wiper Code
Analog Performance Specified for VDD ≥ 2.7V.
FIGURE 2-5:
and Temperature.
DNL vs. Code (00h to 3Fh)
FIGURE 2-7:
and Temperature.
DNL vs. Code (00h to 3Fh)
VDD = 5.5V, VREF = 5.5V, 2.7V, 1.8V, and 1.0V.
VDD = 2.0V, VREF = 2.0V, 1.8V, and 1.0V.
Typical Device
Typical Device
0.50
0.50
0.25
0.00
ꢀ0.25
ꢀ0.50
ꢀ40Cꢁꢀ 1.6V
ꢀ40Cꢁꢀ 1.0V
+25Cꢁꢀ 1.6V
+25Cꢁꢀ 1.0V
+85Cꢁꢀ 1.6V
+85Cꢁꢀ 1.0V
+125Cꢁꢀ 1.6V
+125Cꢁꢀ 1.0V
ꢀ40Cꢁꢀ 2.7V
ꢀ40Cꢁꢀ 1.8V
ꢀ40Cꢁꢀ 1.0V
+25Cꢁꢀ 2.7V
+25Cꢁꢀ 1.8V
+25Cꢁꢀ 1.0V
+85Cꢁꢀ 2.7V
+85Cꢁꢀ 1.8V
+85Cꢁꢀ 1.0V
+125Cꢁꢀ 2.7V
+125Cꢁꢀ 1.8V
+125Cꢁꢀ 1.0V
0.25
0.00
ꢀ0.25
ꢀ0.50
0
8
16
24
32
40
48
56
64
0
8
16
24
32
40
48
56
64
DAC Wiper Code
DAC Wiper Code
Analog Performance Specified for VDD ≥ 2.7V.
FIGURE 2-6:
and Temperature.
DD = 2.7V, VREF = 2.7V, 1.8V, and 1.0V.
DNL vs. Code (00h to 3Fh)
FIGURE 2-8:
and Temperature.
VDD = 1.8V, VREF = 1.6V, and 1.0V.
DNL vs. Code (00h to 3Fh)
V
DS25154A-page 12
2012 Microchip Technology Inc.
MCP47A1
Note: Unless otherwise indicated, TA = +25°C, VDD = VREF = 5V, VSS = 0V, RL = 5 k, CL = 1 nF.
Typical Device
Typical Device
0.00
ꢀ0.20
ꢀ0.40
ꢀ0.60
ꢀ0.80
ꢀ1.00
0.00
ꢀ0.20
ꢀ0.40
ꢀ0.60
ꢀ0.80
ꢀ1.00
ꢀ1.20
ꢀ1.40
ꢀ1.60
WhenꢁVREF =ꢁVDD
FSEꢁꢀ 5.5V
FSEꢁꢀ 2.7V
FSEꢁꢀ 1.8V
FSEꢁꢀ 1.0V
FSEꢁꢀ 2.0V
FSEꢁꢀ 1.8V
FSEꢁꢀ 1.0V
ꢀ40
ꢀ20
0
20
40
60
80
100
120
ꢀ40
ꢀ20
0
20
40
60
80
100
120
Temperature (°C)
Temperature (°C)
Analog Performance Specified for VDD ≥ 2.7V.
FIGURE 2-9:
Full Scale Error (FSE) vs.
FIGURE 2-11:
Full Scale Error (FSE) vs.
Temperature.
Temperature.
VDD = 5.5V, VREF = 5.5V, 2.7V, 1.8V, and 1.0V.
VDD = 2.0V, VREF = 2.0V, 1.8V, and 1.0V.
Typical Device
Typical Device
0.00
0.00
ꢀ1.00
ꢀ2.00
ꢀ3.00
ꢀ4.00
ꢀ5.00
ꢀ0.20
ꢀ0.40
ꢀ0.60
WhenꢁVREF =ꢁVDD
ꢀ0.80
FSEꢁꢀ 2.7V
FSEꢁꢀ 1.6V
FSEꢁꢀ 1.0V
FSEꢁꢀ 1.8V
FSEꢁꢀ 1.0V
ꢀ1.00
ꢀ40
ꢀ20
0
20
40
60
80
100
120
ꢀ40
ꢀ20
0
20
40
60
80
100
120
Temperature (°C)
Temperature (°C)
Analog Performance Specified for VDD ≥ 2.7V.
FIGURE 2-10:
Full Scale Error (FSE) vs.
FIGURE 2-12:
Full Scale Error (FSE) vs.
Temperature.
Temperature.
VDD = 2.7V, VREF = 2.7V, 1.8V, and 1.0V.
VDD = 1.8V, VREF = 1.6V, and 1.0V.
2012 Microchip Technology Inc.
DS25154A-page 13
MCP47A1
Note: Unless otherwise indicated, TA = +25°C, VDD = VREF = 5V, VSS = 0V, RL = 5 k, CL = 1 nF.
Typical Device
Typical Device
1.00
0.80
0.60
0.40
0.20
0.00
1.00
0.80
0.60
0.40
0.20
0.00
ZSEꢁꢀ 2.0V
ZSEꢁꢀ 1.8V
ZSEꢁꢀ 1.0V
ZSEꢁꢀ 5.5V
ZSEꢁꢀ 2.7V
ZSEꢁꢀ 1.8V
ZSEꢁꢀ 1.0V
ꢀ40
ꢀ20
0
20
40
60
80
100
120
ꢀ40
ꢀ20
0
20
40
60
80
100
120
Temperature (°C)
Temperature (°C)
Analog Performance Specified for VDD ≥ 2.7V.
FIGURE 2-13:
Zero Scale Error (ZSE) vs.
FIGURE 2-15:
Zero Scale Error (ZSE) vs.
Temperature.
Temperature.
VDD = 5.5V, VREF = 5.5V, 2.7V, 1.8V, and 1.0V.
VDD = 2.0V, VREF = 2.0V, 1.8V, and 1.0V.
Typical Device
Typical Device
1.00
1.00
0.80
0.60
0.40
0.20
0.00
ZSEꢁꢀ 2.7V
ZSEꢁꢀ 1.6V
ZSEꢁꢀ 1.0V
ZSEꢁꢀ 1.8V
ZSEꢁꢀ 1.0V
0.80
0.60
0.40
0.20
0.00
ꢀ40
ꢀ20
0
20
40
60
80
100
120
ꢀ40
ꢀ20
0
20
40
60
80
100
120
Temperature (°C)
Temperature (°C)
Analog Performance Specified for VDD ≥ 2.7V.
FIGURE 2-14:
Zero Scale Error (ZSE) vs.
FIGURE 2-16:
Zero Scale Error (ZSE) vs.
Temperature.
Temperature.
VDD = 2.7V, VREF = 2.7V, 1.8V, and 1.0V.
VDD = 1.8V, VREF = 1.6V, and 1.0V.
DS25154A-page 14
2012 Microchip Technology Inc.
MCP47A1
Note: Unless otherwise indicated, TA = +25°C, VDD = VREF = 5V, VSS = 0V, RL = 5 k, CL = 1 nF.
Typical Device
Typical Device
1.00
0.75
1.00
0.75
0.50
0.25
0.00
ꢀ0.25
ꢀ0.50
ꢀ0.75
ꢀ1.00
ꢀ40Cꢁꢀ 5.5V
+25Cꢁꢀ 5.5V
+25Cꢁꢀ 2.7V
+25Cꢁꢀ 1.8V
+25Cꢁꢀ 1.0V
+85Cꢁꢀ 5.5V
+125Cꢁꢀ 5.5V
+125Cꢁꢀ 2.7V
+125Cꢁꢀ 1.8V
+125Cꢁꢀ 1.0V
ꢀ40Cꢁꢀ 2.0V
ꢀ40Cꢁꢀ 1.8V
ꢀ40Cꢁꢀ 1.0V
+25Cꢁꢀ 2.0V
+25Cꢁꢀ 1.8V
+25Cꢁꢀ 1.0V
+85Cꢁꢀ 2.0V
+85Cꢁꢀ 1.8V
+85Cꢁꢀ 1.0V
+125Cꢁꢀ 2.0V
+125Cꢁꢀ 1.8V
+125Cꢁꢀ 1.0V
ꢀ40Cꢁꢀ 2.7V
ꢀ40Cꢁꢀ 1.8V
ꢀ40Cꢁꢀ 1.0V
+85Cꢁꢀ 2.7V
+85Cꢁꢀ 1.8V
+85Cꢁꢀ 1.0V
0.50
0.25
0.00
ꢀ0.25
ꢀ0.50
ꢀ0.75
ꢀ1.00
ꢀ1.25
ꢀ1.50
WhenꢁVREF =ꢁVDD
(codeꢁ=ꢁ64)
0
8
16
24
32
40
48
56
64
0
8
16
24
32
40
48
56
64
DAC Wiper Code
DAC Wiper Code
Analog Performance Specified for VDD ≥ 2.7V.
FIGURE 2-17:
Code and Temperature.
DD = 5.5V, VREF = 5.5V, 2.7V, 1.8V, and 1.0V.
Total Unadjusted Error vs.
FIGURE 2-19:
Code and Temperature.
Total Unadjusted Error vs.
V
V
DD = 2.0V, VREF = 2.0V, 1.8V, and 1.0V.
Typical Device
Typical Device
1.00
0.75
0.50
0.25
0.00
ꢀ0.25
ꢀ0.50
ꢀ0.75
ꢀ1.00
1.00
ꢀ40Cꢁꢀ 1.6V
ꢀ40Cꢁꢀ 1.0V
+25Cꢁꢀ 1.6V
+25Cꢁꢀ 1.0V
+85Cꢁꢀ 1.6V
+85Cꢁꢀ 1.0V
+125Cꢁꢀ 1.6V
+125Cꢁꢀ 1.0V
ꢀ40Cꢁꢀ 2.7V
ꢀ40Cꢁꢀ 1.8V
ꢀ40Cꢁꢀ 1.0V
+25Cꢁꢀ 2.7V
+25Cꢁꢀ 1.8V
+25Cꢁꢀ 1.0V
+85Cꢁꢀ 2.7V
+85Cꢁꢀ 1.8V
+85Cꢁꢀ 1.0V
+125Cꢁꢀ 2.7V
+125Cꢁꢀ 1.8V
+125Cꢁꢀ 1.0V
0.00
ꢀ1.00
ꢀ2.00
ꢀ3.00
ꢀ4.00
ꢀ5.00
WhenꢁVREF =ꢁ1.6Vꢁ
(dueꢁtoꢁOutputꢁDriverꢁlinearityꢁatꢁVDD =ꢁ1.8V)
WhenꢁVREF =ꢁVDD
(codeꢁ=ꢁ64)
0
8
16
24
32
40
48
56
64
0
8
16
24
32
40
48
56
64
DAC Wiper Code
DAC Wiper Code
Analog Performance Specified for VDD ≥ 2.7V.
FIGURE 2-18:
Code and Temperature.
DD = 2.7V, VREF = 2.7V, 1.8V, and 1.0V.
Total Unadjusted Error vs.
FIGURE 2-20:
Code and Temperature.
VDD = 1.8V, VREF = 1.6V, and 1.0V.
Total Unadjusted Error vs.
V
2012 Microchip Technology Inc.
DS25154A-page 15
MCP47A1
Note: Unless otherwise indicated, TA = +25°C, VDD = VREF = 5V, VSS = 0V, RL = 5 k, CL = 1 nF.
Typical Device
Typical Device
85.00
80.00
75.00
70.00
65.00
60.00
55.00
50.00
45.00
40.00
35.00
30.00
25.00
20.00
15.00
10.00
5.00
10.00
8.00
PPMꢁ/ꢁCꢁꢀ 2.0V
PPMꢁ/ꢁCꢁꢀ 1.8V
PPMꢁ/ꢁCꢁꢀ 1.0V
PPMꢁ/ꢁCꢁꢀ 5.5V
PPMꢁ/ꢁCꢁꢀ2.7V
PPMꢁ/ꢁCꢁꢀ 1.8V
PPMꢁ/ꢁCꢁꢀ 1.0V
6.00
4.00
2.00
0.00
ꢀ2.00
ꢀ4.00
ꢀ6.00
ꢀ8.00
ꢀ10.00
0.00
ꢀ5.00
ꢀ10.00
0
8
16
24
32
40
48
56
64
0
8
16
24
32
40
48
56
64
DAC Wiper Code
DAC Wiper Code
Analog Performance Specified for VDD ≥ 2.7V.
FIGURE 2-21:
VOUT Tempco vs. Code ( ( (
FIGURE 2-23:
VOUT Tempco vs. Code ( ( (
(VOUT(+125C) - VOUT(-40C) ) / VOUT(+25C,Code=FS)
/ 165 ) * 1,000,000 ),
)
(VOUT(+125C) - VOUT(-40C) ) / VOUT(+25C,Code=FS)
/ 165 ) * 1,000,000 ),
)
VDD = 5.5V, VREF = 5.5V, 2.7V, 1.8V, and 1.0V.
V
DD = 2.0V, VREF = 2.0V, 1.8V, and 1.0V.
Typical Device
Typical Device
350
PPMꢁ/ꢁCꢁꢀ 1.8V
PPMꢁ/ꢁCꢁꢀ 1.0V
14.00
330
310
290
270
250
230
210
190
170
150
130
110
90
PPMꢁ/ꢁCꢁꢀ 2.7V
12.00
PPMꢁ/ꢁCꢁꢀ 1.8V
PPMꢁ/ꢁCꢁꢀ 1.0V
10.00
8.00
6.00
4.00
2.00
0.00
ꢀ2.00
ꢀ4.00
ꢀ6.00
ꢀ8.00
ꢀ10.00
70
50
30
10
ꢀ10
0
8
16
24
32
40
48
56
64
0
8
16
24
32
40
48
56
64
DAC Wiper Code
DAC Wiper Code
Analog Performance Specified for VDD ≥ 2.7V.
FIGURE 2-22:
VOUT Tempco vs. Code ( ( (
FIGURE 2-24:
VOUT Tempco vs. Code ( ( (
(VOUT(+125C) - VOUT(-40C) ) / VOUT(+25C,Code=FS)
/ 165 ) * 1,000,000 ),
)
(VOUT(+125C) - VOUT(-40C) ) / VOUT(+25C,Code=FS)
/ 165 ) * 1,000,000 ),
)
VDD = 2.7V, VREF = 2.7V, 1.8V, and 1.0V.
VDD = 1.8V, VREF = 1.6V, and 1.0V.
DS25154A-page 16
2012 Microchip Technology Inc.
MCP47A1
Note: Unless otherwise indicated, TA = +25°C, VDD = VREF = 5V, VSS = 0V, RL = 5 k, CL = 1 nF.
Typical Device
Typical Device
1.0
0.8
0.6
0.4
0.2
0.0
220
200
180
160
140
120
100
80
VIL 5.5V
VIH 5.5V
VIL 2.7V
VIH 2.7V
VIL 1.8V
VIH 1.8V
400kHz 5.5V
400kHz 3.3V
400kHz 2.7V
400kHz 1.8V
100kHz 1.8V
100kHz 5.5V
100kHz 3.3V
100kHz 2.7V
60
40
-40 -20
0
20
40
60
80 100 120
-40 -20
0
20
40
60
80 100 120
Temperature (°C)
Temperature (C)
FIGURE 2-25:
SDA/SCL Inputs vs. Temperature and VDD
VIH / VIL Threshold of
FIGURE 2-27:
(IDD) vs. SCL Frequency (fSCL) and Temperature
Interface Active Current
.
V
V
DD = 1.8V, 2.7V and 5.5V,
REF = 1.0V and VDD. (no load on VOUT).
Typical Device
0.5
VOL 5.5V
VOL 2.7V
VOL 1.8V
Typical Device
0.4
0.3
0.2
0.1
0.0
220
Static 5.5V
Static 3.3V
Static 2.7V
Static 1.8V
200
180
160
140
120
100
80
-40 -20
0
20
40
60
80 100 120
60
Temperature (°C)
40
-40 -20
0
20
40
60
80 100 120
FIGURE 2-26:
Temperature.
VOL (SDA) vs. VDD and
Temperature (C)
FIGURE 2-28:
Interface Inactive Current
(STATIC) vs. Temperature and VDD
.
V
V
DD = 1.8V, 2.7V and 5.5V, VREF = 1.0V and
DD. (no load on VOUT, SCL = SDA = VDD).
2012 Microchip Technology Inc.
DS25154A-page 17
MCP47A1
Note: Unless otherwise indicated, TA = +25°C, VDD = VREF = 5V, VSS = 0V, RL = 5 k, CL = 1 nF.
Typical Device
Typical Device
5
4
3
2
1
0
5
4
3
2
1
0
Code = 40h
Code = 00h
Code = 40h
0
1000
2000
3000
4000
5000
0
2
4
6
8
10
12
14
I
SOURCE/SINK (mA)
I
SOURCE/SINK (mA)
FIGURE 2-29:
VOUT vs. Resistive Load.
FIGURE 2-31:
VOUT vs. Source / Sink
VDD = 5.0V.
Current. VDD = 5.0V.
Typical Device
Typical Device
2.7
2.7
1.8
0.9
0.0
Code = 40h
Code = 00h
Code = 40h
1.8
0.9
0.0
0
1000
2000
3000
4000
5000
0
2
4
6
8
10
12
14
I
SOURCE/SINK (mA)
ISOURCE/SINK (mA)
FIGURE 2-30:
DD = 2.7V.
VOUT vs. Resistive Load.
FIGURE 2-32:
Current. VDD = 2.7V.
VOUT vs. Source / Sink
V
DS25154A-page 18
2012 Microchip Technology Inc.
MCP47A1
Note: Unless otherwise indicated, TA = +25°C, VDD = VREF = 5V, VSS = 0V, RL = 5 k, CL = 1 nF.
Typical Device
0.78
0.77
0.76
0.75
0.74
0.73
0.72
VOUT 5.5V
VOUT 2.7V
-40 -20
0
20
40
60
80 100 120
Temperature (C)
FIGURE 2-33:
VOUT Accuracy vs. VDD and
Temperature.
Typical Device
23000
22000
21000
20000
19000
18000
RVREF5.5V
RVREF 2.7V
RVREF 1.8V
17000
-40 -20
0
20 40 60 80 100 120
Temperature (°C)
Analog Performance Specified for VDD ≥ 2.7V.
FIGURE 2-34:
RVREF Resistances vs. VDD
and Temperature.
Typical Device
3.00
0.00
ꢀ3.00
ꢀ6.00
ꢀ9.00
ꢀ12.00
ꢀ15.00
ꢀ18.00
ꢀ21.00
ꢀ24.00
ꢀ27.00
ꢀ30.00
FullꢀScaleꢁꢀ VREFꢁ=ꢁ2.7V
MidꢀScaleꢁVREFꢁ=ꢁ2.7V
QuarterꢁScaleꢁVREFꢁ=ꢁ2.7V
FullꢀScaleꢁVREFꢁ=ꢁ5.5V
MidꢀScaleꢁVREFꢁ=ꢁ5.5V
QuarterꢁScaleꢁVREFꢁ=ꢁ5.5V
1
10
100
1000
Frequency (kHz)
FIGURE 2-35:
-3dB Bandwidth vs
Frequency, VDD = 5.5V.
2012 Microchip Technology Inc.
DS25154A-page 19
MCP47A1
Note: Unless otherwise indicated, TA = +25°C, VDD = VREF = 5V, VSS = 0V, RL = 5 k, CL = 1 nF.
FIGURE 2-36:
Settling Time (00h to 40h),
DD = 5.0V, VREF = 5.0V, RL = 5k, CL = 200 pF
(Time scale = 2 µs / div).
Zero-Scale to Full-Scale
FIGURE 2-38:
(10h to 30h),
Half-Scale Settling Time
V
V
DD = 5.0V, VREF = 5.0V, RL = 5k, CL = 200 pF.
(Time scale = 2 µs / div)
FIGURE 2-37:
Full-Scale to Zero-Scale
FIGURE 2-39:
Half-Scale Settling Time
Settling Time (40h to 00h),
(30h to 10h),
VDD = 5.0V, VREF = 5.0V, RL = 5k, CL = 200 pF
V
DD = 5.0V, VREF = 5.0V, RL = 5k, CL = 200 pF
(Time scale = 2 µs / div).
(Time scale = 2 µs / div).
DS25154A-page 20
2012 Microchip Technology Inc.
MCP47A1
Note: Unless otherwise indicated, TA = +25°C, VDD = VREF = 5V, VSS = 0V, RL = 5 k, CL = 1 nF.
2.1
Test Circuit
VDD
VREF
VIN
4.0V
(peak to
peak)
W
VOUT
+
-
1.0V DC
FIGURE 2-41:
-3 db Gain vs. Frequency
Test.
FIGURE 2-40:
Digital Feedthrough
(SCL signal coupling to VOUT pin);
VDD = 5.0V, VREF = 5.0V, FSCL = 100 kHz,
VOUT = 20h (VOUT Voltage Scale = 20 mV/div,
Time scale = 2 µs / div).
2012 Microchip Technology Inc.
DS25154A-page 21
MCP47A1
NOTES:
DS25154A-page 22
2012 Microchip Technology Inc.
MCP47A1
3.0 PIN DESCRIPTIONS
The descriptions of the pins are listed in Table 3-1.
Additional descriptions of the device pins follow.
TABLE 3-1:
PINOUT DESCRIPTION FOR THE MCP47A1
Package
Pin
Name
Pin
Type
Buffer
Type
Function
SC70-6
VDD
VSS
1
2
3
4
5
P
—
—
Positive Power Supply Input
Ground
P
SCL
SDA
VOUT
I/O
I/O
I/O
ST (OD) I2C Serial Clock pin
ST (OD) I2C Serial Data pin
A
A
Output voltage
VREF
6
I/O
Reference Voltage for VOUT output
Legend: A = Analog input
ST (OD) = Schmitt Trigger with Open Drain
I = Input
O = Output
I/O = Input/Output
P = Power
3.1
Positive Power Supply Input (V
)
3.5
Analog Output Voltage Pin (V
)
DD
OUT
The VDD pin is the device’s positive power supply input.
The input power supply is relative to VSS and can range
from 1.8V to 5.5V. A decoupling capacitor on VDD
VOUT is the DAC analog output pin. The DAC output
has an output amplifier.
VOUT can swing from approximately VZS (= VSS) to VFS
(= VREF). In normal mode, the DC impedance of the
output pin is about 1 . See Section 7.0 “Output
Buffer” for more information.
(to VSS) is recommended to achieve maximum
performance. Analog specifications are tested from
2.7V.
3.2
Ground (V
)
SS
3.6
Voltage Reference Pin (V
)
REF
The VSS pin is the device ground reference.
This pin is the external voltage reference input. The
VREF pin signal is unbuffered so the reference voltage
must have the current capability not to drop its voltage
when connected to the internal resistor ladder circuit
(20 k typical). See Section 6.0 “Resistor Network”
for more information.
2
3.3
I C Serial Clock (SCL)
The SCL pin is the serial clock pin of the I2C interface.
The MCP47A1 acts only as a slave and the SCL pin
accepts only external serial clocks. The SCL pin is an
open-drain output. Refer to Section 5.0 “Serial
Interface - I2C Module” for more details of I2C Serial
Interface communication.
2
3.4
I C Serial Data (SDA)
The SDA pin is the serial data pin of the I2C interface.
The SDA pin has a Schmitt trigger input and an
open-drain output. Refer to Section 5.0 “Serial
Interface - I2C Module” for more details of I2C Serial
Interface communication.
2012 Microchip Technology Inc.
DS25154A-page 23
MCP47A1
NOTES:
DS25154A-page 24
2012 Microchip Technology Inc.
MCP47A1
4.0
GENERAL OVERVIEW
VREF
The MCP47A1 device is a general purpose DAC
intended to be used in applications where a program-
mable voltage output with moderate bandwidth is
desired.
A
RFS
Applications generally suited for the MCP47A1 devices
include:
(1)
(1)
RW
RW
RS
• Set point or offset trimming
• Sensor calibration
RS
• Cost-sensitive mechanical trim pot replacement
Goes to Output
Buffer’s input
The MCP47A1 has four main functional blocks. These
are:
W
• POR/BOR Operation
• Serial Interface - I2C Module
• Resistor Network
(1)
(1)
RW
RW
RS
• Output Buffer
The POR/BOR operation is discussed in this section
and the I2C and Resistor Network operation are
described in their own sections. The commands are
discussed in Section 5.3, Serial Commands.
RZS
Analog Switch Mux
B
Figure 4-1 shows a block diagram for the resistive
network of the device. An external pin, called VREF, is
the DAC’s reference voltage. The resistance from the
VREF pin to ground is typically 20 k. The reference
voltage connected to the VREF pin needs to support this
resistive load.
+
Op Amp
VOUT
-
This resistor network functions as a windowed voltage
divider. This means that the VOUT pin’s voltage range is
from approximately VSS to approximately VREF
.
Note 1: The wiper resistance is tap dependent.
That is, each tap selection resistance
has a small variation.
2: The RFS and RZS resistances are
determined by the analog switches that
connect the resistor network to the other
circuitry.
FIGURE 4-1:
Resistor Network and
Output Buffer Block Diagram.
2012 Microchip Technology Inc.
DS25154A-page 25
MCP47A1
4.1.2
BROWN-OUT RESET
4.1
POR/BOR Operation
When the device powers down, the device VDD will
cross the VPOR/VBOR voltage (VBOR < 1.8V). Once the
VDD voltage decreases below the VPOR/VBOR voltage,
the following happens:
The Power-on Reset is the case where the device has
power applied to it from VSS. The Brown-out Reset
occurs when a device had power applied to it, and that
power (voltage) drops below the specified range.
• Serial Interface is disabled
The device’s RAM retention voltage (VRAM) is lower
than the POR/BOR voltage trip point (VPOR/VBOR).
This ensures that when the device Power-on Reset
occurs, the logic can retain default values that are
loaded. The maximum VPOR/VBOR voltage is less than
1.8V. When VPOR/VBOR < VDD < 1.8V, the DACs’ elec-
trical performance may not meet the data sheet
specifications.
If the VDD voltage decreases below the VRAM voltage,
the following happens:
• Volatile Serial Shift Register (SSR) and Wiper
register may become corrupted
As the voltage recovers above the VPOR/VBOR voltage,
see Section 4.1.1 “Power-on Reset”.
Serial commands not completed due to a Brown-out
condition may cause the memory location to become
corrupted.
Table 4-2 shows the DAC’s level of functionality across
the entire VDD range, while Figure 4-2 illustrates the
Power-up and Brown-out functionality.
4.1.3
WIPER REGISTER (RAM)
4.1.1
POWER-ON RESET
The Wiper Register is 7-bit volatile memory that starts
functioning at the RAM retention voltage (VRAM). The
Wiper Register will be loaded with the default wiper
value when VDD rises above the VPOR/VBOR voltage.
When the device powers up, the device VDD will cross
the VPOR/VBOR voltage. Once the VDD voltage crosses
the VPOR/VBOR voltage, the following happens:
• Volatile Serial Shift Register / Wiper register is
loaded with the default values (see Table 4-1)
4.1.4
DEVICE CURRENTS
• The device is capable of digital operation
The current of the device can be classified into two
modes of the device operation. These are:
Note:
At voltages below VDD(MIN), the electrical
performance of the I2C interface may not
meet the data sheet specifications
• Serial Interface Inactive (Static Operation)
• Serial Interface Active
Static Operation occurs when a Stop condition is
received. Static Operation is exited when a Start
condition is received.
TABLE 4-1:
DEFAULT POR WIPER
SETTING SELECTION
Default POR
Wiper Setting Register (SSR)
Serial Shift
Wiper Register
Mid-scale
20h
20h
TABLE 4-2:
VDD Level
DEVICE FUNCTIONALITY AT EACH VDD REGION (Note 1)
Serial
VOUT
DAC Register Setting
Comment
Interface
V
DD < VTH
Ignored
“Unknown”
Pulled Low
Unknown
Unknown
VTH < VDD < VBOR Ignored
VBOR VDD < 1.8V “Unknown” Operational with reduced DAC Register loaded with
electrical specifications POR/BOR value
1.8V VDD 5.5V Accepted Operational DAC Register determines Meets the data sheet
Serial Value specifications
Note 1: For system voltages below the minimum operating voltage, it is recommended to use a voltage supervisor
to hold the system in reset. This will ensure that MCP47x1 commands are not attempted out of the oper-
ating range of the device.
DS25154A-page 26
2012 Microchip Technology Inc.
MCP47A1
Normal Operation Range
VDD
Outside Specified
AC/DC Range
Normal Operation Range
1.8V
VPOR/BOR
VRAM
VSS
Below Minimum Operating Voltage
Device’s Serial
Interface is
“Not Operational”
VBOR delay
Wiper forced to default POR/BOR setting
FIGURE 4-2:
Power-up and Brown-out.
2012 Microchip Technology Inc.
DS25154A-page 27
MCP47A1
NOTES:
DS25154A-page 28
2012 Microchip Technology Inc.
MCP47A1
2
5.1
I C I/O Considerations
5.0
SERIAL INTERFACE -
I C MODULE
2
I2C specifications require active low, passive high
functionality on devices interfacing to the bus. Since
devices may be operating on separate power supply
sources, ESD clamping diodes are not permitted. The
specification recommends using open drain transistors
tied to VSS (common) with a pull-up resistor. The
specification makes some general recommendations
on the size of this pull-up, but does not specify the
exact value since bus speeds and bus capacitance
impacts the pull-up value for optimum system
performance.
A 2-wire I2C serial protocol is used to write or read the
DAC’s wiper register. The I2C protocol utilizes the SCL
input pin and SDA input/output pin.
The I2C serial interface supports the following features:
• Slave mode of operation
• 7-bit addressing
• The following clock rate modes are supported:
- Standard mode, bit rates up to 100 kb/s
- Fast mode, bit rates up to 400 kb/s
• Support Multi-Master Applications
Common pull-up values range from 1 k to a maximum
of ~10 k. Power sensitive applications tend to choose
higher values to minimize current losses during
communication but these applications also typically
The serial clock is generated by the Master.
The I2C Module is compatible with the NXP I2C
specification (# UM10204). Only the field types, field
lengths, timings, etc. of a frame are defined. The frame
content defines the behavior of the device. The frame
content for the MCP47A1 device is defined in this sec-
tion of the data sheet.
utilize lower VDD
.
The SDA and SCL float (are not driving) when the
device is powered down.
A "glitch" filter is on the SCL and SDA pins when the pin
is an input. When these pins are an output, there is a
slew rate control of the pin that is independent of device
frequency.
Figure 5-1 shows a typical I2C bus configuration.
Single I2C Bus Configuration
5.1.1
SLOPE CONTROL
The device implements slope control on the SDA
output. The slope control is defined by the fast mode
specifications.
Device 1
Device 3
Device n
Host
Controller
For Fast (FS) mode, the device has spike suppression
and Schmidt trigger inputs on the SDA and SCL pins.
Device 4
Typical Application I2C Bus
Device 2
FIGURE 5-1:
Configurations.
Refer to Section 2.0 “Typical Performance Curves”,
AC/DC Electrical Characteristics table for detailed input
threshold and timing specifications.
2012 Microchip Technology Inc.
DS25154A-page 29
MCP47A1
2
If the Slave Address is not valid, the Slave Device will
issue a Not A (A). The A bit will have the SDA signal
high.
5.2
I C Bit Definitions
I2C bit definitions include:
• Start Bit
If an error condition occurs (such as an A instead of A)
then a START bit must be issued to reset the command
state machine.
• Data Bit
• Acknowledge (A) Bit
• Repeated Start Bit
• Stop Bit
TABLE 5-1:
Event
MCP47A1 A / A RESPONSES
• Clock Stretching
Acknowledge
Comment
Bit Response
Figure 5-8 shows the waveform for these states.
General Call
A
A
5.2.1
START BIT
SlaveAddress
valid
The Start bit (see Figure 5-2) indicates the beginning of
a data transfer sequence. The Start bit is defined as the
SDA signal falling when the SCL signal is “High”.
SlaveAddress
not valid
A
Bus Collision
N.A.
I2C Module Resets,
or a “Don’t Care” if
the collision occurs
on the Masters
“Start bit”.
2nd Bit
1st Bit
SDA
SCL
S
FIGURE 5-2:
Start Bit.
5.2.4
REPEATED START BIT
The Repeated Start bit (see Figure 5-5) indicates
the current Master Device wishes to continue
communicating with the current Slave Device without
releasing the I2C bus. The Repeated Start condition is
the same as the Start condition, except that the
Repeated Start bit follows a Start bit (with the Data bits
+ A bit) and not a Stop bit.
5.2.2 DATA BIT
The SDA signal may change state while the SCL signal
is Low. While the SCL signal is High, the SDA signal
MUST be stable (see Figure 5-3).
2nd Bit
1st Bit
SDA
The Start bit is the beginning of a data transfer
sequence and is defined as the SDA signal falling when
the SCL signal is “High”.
SCL
Note 1: A bus collision during the Repeated Start
FIGURE 5-3:
Data Bit.
condition occurs if:
• SDA is sampled low when SCL goes
from low to high.
5.2.3
ACKNOWLEDGE (A) BIT
The A bit (see Figure 5-4) is a response from the Slave
device to the Master device. Depending on the context
of the transfer sequence, the A bit may indicate
different things. Typically the Slave device will supply
an A response after the Start bit and 8 “data” bits have
been received. The A bit will have the SDA signal low.
• SCL goes low before SDA is
asserted low. This may indicate that
another master is attempting to
transmit a data "1".
1st Bit
SDA
D0
A
SDA
SCL
8
9
SCL
FIGURE 5-4:
Acknowledge Waveform.
Sr = Repeated Start
FIGURE 5-5:
Repeat Start Condition
Waveform.
DS25154A-page 30
2012 Microchip Technology Inc.
MCP47A1
5.2.5
STOP BIT
5.2.7
ABORTING A TRANSMISSION
The Stop bit (see Figure 5-6) indicates the end of the
I2C Data Transfer Sequence. The Stop bit is defined as
the SDA signal rising when the SCL signal is “High”.
A Stop bit resets the I2C interface of the other devices.
If any part of the I2C transmission does not meet the
command format, it is aborted. This can be intentionally
accomplished with a START or STOP condition. This is
done so that noisy transmissions (usually an extra
START or STOP condition) are aborted before they
corrupt the device.
A / A
SDA
SCL
5.2.8
IGNORING AN I2C TRANSMISSION
AND “FALLING OFF” THE BUS
The MCP47A1 expects to receive entire, valid I2C com-
mands and will assume any command not defined as a
valid command is due to a bus corruption, and will enter
a passive high condition on the SDA signal. All signals
will be ignored until the next valid START condition and
CONTROL BYTE are received.
P
FIGURE 5-6:
Transmit Mode.
Stop Condition Receive or
5.2.6
CLOCK STRETCHING
“Clock Stretching” is something that the secondary
device can do, to allow additional time to “respond” to
the “data” that has been received.
The MCP47A1 will not stretch the clock signal (SCL)
since memory read accesses occur fast enough.
SDA
SCL
S
1st 2nd 3rd 4th 5th 6th 7th 8th A/A 1st 2nd 3rd 4th 5th 6th 7th 8th A/A
P
Bit Bit Bit Bit Bit Bit Bit Bit
Bit Bit Bit Bit Bit Bit Bit Bit
FIGURE 5-7:
Typical 16-bit I2C Waveform Format.
SDA
SCL
START
Condition
Data allowed
to change
Data or
A valid
STOP
Condition
FIGURE 5-8:
I2C Data States and Bit Sequence.
2012 Microchip Technology Inc.
DS25154A-page 31
MCP47A1
5.2.9
I2C COMMAND PROTOCOL
TABLE 5-2:
Device
DEVICE I2C ADDRESS
I2C Address
The MCP47A1 is a slave I2C device which supports 7-
bit slave addressing. The slave address contains seven
fixed bits. Figure 5-9 shows the control byte format.
Binary
‘0101110’ 0x5C
‘0111110’ 0x7C
Hex (1) Code Comment
A0
A1
MCP47A1
5.2.9.1
Control Byte (Slave Address)
Note 1: The LSb of the 8-bit hex code is the I2C
Read/Write (R/W) bit. This hex value has
a R/W bit = “0” (write). If the R/W bit
reflected a read, these values would be
0x5D and 0x7D.
The Control Byte is always preceded by a START
condition. The Control Byte contains the slave address
consisting of seven fixed bits and the R/W bit. Figure 5-
9 shows the control byte format and Table 5-2 shows
the I2C address for the devices.
Note 1: The MCP47A1 device supports two differ-
ent I2C address (A0 and A1). This allows
two MCP47A1 devices on the same I2C
bus.
Slave Address
S
A6 A5 A4 A3 A2 A1 A0 R/W
“0”“1” “0”“1” “1” “1”“0”
A/A
5.2.9.2
Hardware Address Pins
Start
bit
The MCP47A1 does not support hardware address
bits.
R/W bit
R/W = 0= write
R/W = 1= read
5.2.10
GENERAL CALL
A bit (controlled by slave device)
The General Call is a method that the Master device
can communicate with all other Slave devices.
A = 0= Slave Device Acknowledges byte
A = 1= Slave Device does not Acknowledge byte
The MCP47A1 devices do not respond to General Call
address and commands, and therefore the
communications are Not Acknowledged.
FIGURE 5-9:
Slave Address Bits in the
I2C Control Byte.
Second Byte
0 0 0 0 0 0 0 0
0
A
S
A
X X
X
X
X
X
X
P
General Call Address
“7-bit Command”
Reserved 7-bit Commands (By I2C Specification - NXP specification # UM10204, Ver. 03 16 January 2007)
“0000 011”b- Reset and write programmable part of slave address by hardware
“0000 010”b- Write programmable part of slave address by hardware
“0000 000”b- NOT Allowed
The Following is a “Hardware General Call” Format
Second Byte
n occurrences of (Data + A / A)
A X X X X A P
0 0 0 0 0 0 0 0
S
A
X X
X
X
X
X
X
1
X
X
X
X
General Call Address
“7-bit Command”
This indicates a “Hardware General Call”.
MCP47A1 will ignore this byte and
all following bytes (and A), until
a Stop bit (P) is encountered.
FIGURE 5-10:
General Call Formats.
DS25154A-page 32
2012 Microchip Technology Inc.
MCP47A1
5.3.2
READ OPERATIONS
5.3
Serial Commands
The read operation requires the START condition,
Control Byte, Acknowledge, Command Code,
Acknowledge, Restart Condition, Control Byte,
Acknowledge, Data Byte, the master generating the
A and STOP (or RESTART) condition. The first Control
Byte requires the R/W bit equal to a logic zero (R/W =
“0”) to write the Command Code, while the second
Control Byte requires the R/W bit equal to a logic one
(R/W = “1”) to generate a read sequence. The
MCP47A1 will A the Slave Address Byte and A all the
Data Bytes. The I2C Master will A the Slave Address
Byte and the last Data Byte. If there are multiple Data
Bytes, the I2C Master will A all Data Bytes except the
last Data Byte (which it will A).
The MCP47A1 devices support two serial commands.
These commands are:
• Write Operation
• Read Operations
The I2C command formats have been defined to
support the SMBus version 2.0 Write Byte/Word
Protocol formats and Read Byte/Word Protocol
formats. The SMBus specification that defines this
operation is Section 5 of the Version 2.0 document
(August 3, 2000).
This protocol format may be convenient for customers
using library routines for the I2C bus, where all they
need to do is specify the command (read, write, ...) with
the Device Address, the Register Address, and the
Data.
The MCP47A1 maintains control of the SDA signal until
all data bits have been clocked out.
The command is terminated once a Stop (P) or Restart
(S) condition occurs. Refer to Figure 5-14 for the read
command sequence. For a single read, the master
sends a STOP or RESTART condition after the 1st data
byte (and A bit) is sent from the slave.
5.3.1
WRITE OPERATION
The write operation requires the START condition,
Control Byte, Acknowledge, Command Code,
Acknowledge, Data Byte, Acknowledge and STOP (or
RESTART) condition. The Control (Slave Address)
Byte requires the R/W bit equal to a logic zero (R/W =
“0”) to generate a write sequence. The MCP47A1 is
responsible for generating the Acknowledge (A) bits.
The MSb of each Data Byte is always a “0”, since the
wiper register is only 7-bits wide.
Figure 5-15 shows the I2C read communication
behavior of the Master Device and the MCP47A1
device and the resultant I2C bus values.
Data is written to the MCP47A1 after every byte
transfer (during the A bit). If a STOP or RESTART
condition is generated during a data transfer (before
the A bit), the data will not be written to MCP47A1.
Note:
A command code with a non-zero value
will cause the data not to be read from the
wiper register
Data bytes may be written after each Acknowledge.
The command is terminated once a Stop (P) condition
occurs. Refer to Figure 5-11 for the single byte write
sequence and Figure 5-12 for the generic (multi-byte)
write sequence. For a single byte write, the master
sends a STOP or RESTART condition after the 1st data
byte is sent.
The MSb of each Data Byte is a don’t care, since the
wiper register is only 7-bits wide.
The command is terminated once a Stop (P) or Restart
(S) condition occurs.
Figure 5-13 shows the I2C write communication
behavior of the Master Device and the MCP47A1
device and the resultant I2C bus values.
Note:
A command code with a non-zero value
will cause the data not to be written to the
wiper register
2012 Microchip Technology Inc.
DS25154A-page 33
MCP47A1
Fixed
Address
Read/Write bit (“0”= Write)
STOP bit
0
0
0
0
P
S 0 1 0 1 1 1 0 0 A
Slave Address Byte (1)
0
0
0
0
A X D6 D5 D4 D3 D2 D1 D0 A
Data Byte
Command Code
Legend
S = Start Condition
P = Stop Condition
A = Acknowledge
X = Don’t Care
R/W = Read/Write bit
D6:D0 = Data bits
Note 1: Example using Slave Address Option A0 (5Ch).
FIGURE 5-11:
I2C Single Byte Write Command Format.
Fixed
Address
Read/Write bit (“0”= Write)
0
0
0 0
S 0 1 0 1 1 1 1 0 A
0
0
0
0
A X D6 D5 D4 D3 D2 D1 D0 A
Slave Address Byte (1)
Command Code
Data Byte
STOP bit
X D6 D5 D4
P
D3 D2 D1 D0 A X D6 D5 D4 D3 D2 D1 D0 A
Data Byte Data Byte
Legend
S = Start Condition
P = Stop Condition
A = Acknowledge
X = Don’t Care
R/W = Read/Write bit
D6:D0 = Data bits
Note 1: Example using Slave Address Option A0 (5Ch).
FIGURE 5-12:
I2C Write Command Format.
DS25154A-page 34
2012 Microchip Technology Inc.
MCP47A1
Write 1 Byte with Command Code = 00h
R A
A
A
/
C
C
C
S Slave Address
W K Command Code
K Data Byte
K P
Master
S 0 1 0 1 1 1 0 0 1 0 0 0 0 0 0 0 0 1 0 d d d d d d d 1 P
MCP47A1
I2C Bus
0
0
0
S 0 1 0 1 1 1 0 0 0 0 0 0 0 0 0 0 0 0 0 d d d d d d d 0 P
Write 2 Byte with Command Code = 00h
R A
A
C
A
C
K
/
C
S Slave Address
W K Command Code
K Data Byte
Master
S 0 1 0 1 1 1 0 0 1 0 0 0 0 0 0 0 0 1 0 d d d d d d d 1
MCP47A1
I2C Bus
0
0
0
S 0 1 0 1 1 1 0 0 0 0 0 0 0 0 0 0 0 0 0 d d d d d d d 0
A
C
Data Byte
K P
Master
0 d d d d d d d 1 P
MCP47A1
I2C Bus
0
0 d d d d d d d 0 P
FIGURE 5-13:
I2C Write Communication Behavior.
2012 Microchip Technology Inc.
DS25154A-page 35
MCP47A1
Read/Write bit (“0”= Write)
0
0
0 0
S
0
1
0
1
1
1
0
0 A
0
0
0 0 A
Legend
S = Start Condition
Slave Address Byte (3)
Command Code
Read/Write bit (“1”= Read)
P = Stop Condition
A = Acknowledge
X = Don’t Care
STOP bit
(2) P
0
1
0 1
S
1
1
0
1 A 0 D6 D5 D4 D3 D2 D1 D0 A
R/W = Read/Write bit
D6:D0 = Data bits
Slave Address Byte (3)
Data Byte
Note 1: Master Device is responsible for ACK / NACK signal. If a NACK signal occurs, the MCP47A1 will abort this transfer
and release the bus.
2: The Master Device will Not ACK, and the MCP47A1 will release the bus so the Master Device can generate a Stop or
Repeated Start condition.
3: Example using Slave Address Option A0 (5Ch).
FIGURE 5-14:
I2C Read Command Format.
Read 1 Byte with Command Code = 00h
R A
A
R A
/
C
C R
/ C
S Slave Address
W K Command Code
K S Slave Address
W K
Master
S 0 1 0 1 1 1 0 0 1 0 0 0 0 0 0 0 0 1 S 0 1 0 1 1 1 0 1 1
MCP47A1
I2C Bus
0
0
0
S 0 1 0 1 1 1 0 0 0 0 0 0 0 0 0 0 0 0 S 0 1 0 1 1 1 0 1 0
A
C
Data Byte
K P
Master
1 P
MCP47A1
0 d d d d d d d 1
I2C Bus
0 d d d d d d d 1 P
Read 2 Byte with Command Code = 00h
R A
A
R A
/
C
C R
/ C
S Slave Address
W K Command Code
K S Slave Address
W K
Master
S 0 1 0 1 1 1 0 0 1 0 0 0 0 0 0 0 0 1 S 0 1 0 1 1 1 0 1 1
MCP47A1
I2C Bus
0
0
0
S 0 1 0 1 1 1 0 0 0 0 0 0 0 0 0 0 0 0 S 0 1 0 1 1 1 0 1 0
A
A
C
C
Data Byte
K Data Byte
K P
Master
0
1 P
MCP47A1
I2C Bus
0 d d d d d d d 1 0 d d d d d d d 1
0 d d d d d d d 0 0 d d d d d d d 1 P
FIGURE 5-15:
I2C Read Communication Behavior.
DS25154A-page 36
2012 Microchip Technology Inc.
MCP47A1
6.2
R
Resistor Ladder
AB
6.0
RESISTOR NETWORK
The RAB resistor ladder is a digital potentiometer in a
voltage divider configuration. The RAB resistor ladder
has 64 RS resistors in series. This resistor ladder has
65 wiper taps which allow wiper connectivity to the
bottom (terminal B), Zero-Scale, and the top (terminal
A), Full-Scale, of the resistor ladder (see Figure 6-1).
With an even number of RS resistors in the RAB ladder,
when the wiper is at the Mid-Scale value, VOUT equals
VREF / 2. The RAB resistance also includes the RFS and
The Resistor Network is made up of an RAB resistor
ladder. The RAB resistor has a typical resistance of
20 k. Figure 6-1 shows a block diagram for the
resistor network and output buffer. The resistance from
the VREF pin to ground is referred to as RVREF
.
The 7-bit I2C Data Byte (00h - 7Fh) is decoded to the 6-
bit wiper value (00h - 40h). Section 6.3 describes the
Serial Shift buffer to Wiper register decoding.
R
ZS resistances (see Section 6.2.2). The RAB (and RS)
6.1
R
Resistance
VREF
resistance has small variations over voltage and
temperature. The typical RAB resistance is 10k .
RVREF resistance is the resistance from the VREF pin to
ground and is the RAB resistances. Equation 6-1 shows
6.2.1
THE WIPER
how to calculate RVREF
.
The value in the volatile wiper register selects which
analog switch to close, connecting the W terminal to
the selected node of the resistor ladder. The Wiper reg-
ister value is derived from the Serial Shift Register
value (see Section 6.3).
6.1.1 VREF PIN CURRENT (IVREF
)
The current into the VREF pin is dependent on the volt-
age on the VREF pin (VREF) and the RVREF resistance.
The VREF pin’s voltage source current capability should
support a resistive load that is the minimum RVREF
resistance.
Any variation of the wiper resistance does not effect the
voltage at the W terminal, and therefore the input of the
output buffer.
EQUATION 6-1:
(VREF
CALCULATING RVREF
6.2.2
RFS AND RZS RESISTORS
)
The RFS and RZS resistances are artifacts of the RAB
resistor implementation. These resistors are included
in the block diagram to help better model the actual
device operation. Equation 6-2 shows how to estimate
the RS, RFS, and RZS resistances, based on the
measured voltages of VREF, VFS, and VZS and the
RVREF
=
(IVREF
)
VREF is the voltage on the VREF pin.
VREF is the current into the VREF pin.
I
measured current IVREF
.
EQUATION 6-2:
ESTIMATING RS, RFS
AND RZS
,
VREF
RFS
=
=
IVREF
VZS
RZS
IVREF
VS
RS =
IVREF
Where:
VS =
( VFS - VZS
64
)
VFS is the VOUT voltage when the wiper code is at
full-scale.
VZS is the VOUT voltage when the wiper code is at
zero-scale.
2012 Microchip Technology Inc.
DS25154A-page 37
MCP47A1
VREF
A
RFS
N = 64
(40h)
(1)
RW
RS
RS
RS
N = 63
(3Fh)
(1)
(1)
RW
RW
N = 62
(3Eh)
W
+
Op Amp
VOUT
N = 1
(01h)
-
(1)
(1)
RW
RW
RS
N = 0
(00h)
Output Buffer
(Section 7.0)
Analog
Mux
RZS
B
Wiper Value
Resistor Network (Section 6.0)
Note 1: The wiper resistance is tap dependent. That is, each tap selection resistance has a
small variation.
FIGURE 6-1:
Resistor Network and Output Buffer Block Diagram.
DS25154A-page 38
2012 Microchip Technology Inc.
MCP47A1
6.3
Serial Buffer to Wiper Register
Decode
6.4
Resistor Variations
(Voltage and Temperature)
The I2C’s Data Byte is 8-bits, where only the lower 7-
bits are implemented. This register is called the Serial
Shift Register (SSR). The Wiper register supports
addressing of 65 taps (6-bit resolution). Table 6-1
shows the decoding of the Serial Shift Register to the
Wiper Register value.
The RAB resistors are implemented to have minimal
variations (by design). Any variations should occur
uniformly on all the resistor elements, so the resistor’s
elements will track each other over temperature and
process variations.
The variation of the resistive elements over the operat-
ing voltage range is also minimal. Therefore the VREF
resistance (RVREF) of the device has minimal variation
due to operating voltage.
Note 1: The I2C Write and Read commands
access the value in the Serial Shift Regis-
ter (SSR).
2: The MSb of the I2C Data Byte is ignored
and not loaded into the SSR. A write of
C0h, will result in the same VOUT voltage
as a write of 40h (mid-scale). A subse-
quent read command (of the SSR) will
result in a value of 40h.
Since the VOUT pin’s voltage is ratiometric, and the
resistive elements change uniformly over temperature,
process, and operating voltage variations. Minimal
variation should be seen on the VOUT pin’s voltage.
6.5
POR Value
3: The 7-bit SSR value is decoded to a 6-bit
(65 taps) value that controls the wiper’s
position.
A POR/BOR event will load the volatile Serial Shift
Register (and therefore Wiper register) with the default
value. Table 6-2 shows the default values offered.
TABLE 6-1:
SERIAL SHIFT REGISTER
VALUE TO WIPER VALUE
TABLE 6-2:
Device
POR/BOR SETTINGS
Register Value (1)
I2C Write
Data
Wiper
Setting
SSR(1)
Comment
Value(2)
SSR
Wiper
MCP47A1
Mid-scale
20h or A0h
20h
00h
00h
00h
Wiper Register at
Zero Scale,
VOUT = VSS
Note 1: Custom POR/BOR Wiper Setting options
are available; contact the local Microchip
Sales Office for additional information.
Custom options have NRE and minimum
volume requirements.
01h or 81h
02h or 82h
01h
02h
:
01h
02h
:
:
20h or A0h
20h
20h
Mid-Scale (POR
value),
VOUT = (1/2) * VREF
:
:
:
3Eh or BEh 3Eh
3Eh
Wiper Register =
SSR - 20h
3Fh or BFh 3Fh
3Fh
40h
Wiper Register =
SSR - 20h
40h - 7Fh or 40h -
C0h - FFh 7Fh
Wiper Register at
Full Scale,
VOUT = VREF
Note 1: The Serial Shift Register (SSR) is 7-bits
wide and holds the value written from the
I2C Write command. An I2C Read com-
mand will read the value in this register.
2: The Wiper value is the value that controls
the resistor ladder’s wiper position.
2012 Microchip Technology Inc.
DS25154A-page 39
MCP47A1
NOTES:
DS25154A-page 40
2012 Microchip Technology Inc.
MCP47A1
7.1.1
OUTPUT VOLTAGE
7.0
OUTPUT BUFFER
The volatile DAC Register’s value controls the analog
VOUT voltage. The volatile Wiper Register’s value is
unsigned binary. The formula for the output voltage is
given in Equation 7-1.
As the device powers up, the VOUT pin will float to an
unknown value. When the device’s VDD is above the
transistor threshold voltage of the device, the output
will start being pulled low. After the VDD is above the
POR/BOR trip point (VBOR/VPOR), the resistor net-
work’s wiper will be loaded with the POR value (20h,
which is midscale). The output voltage of the buffer
(VOUT) may not be within specification until the device
VDD is at 2.7V. The outputs’ slew rate and settling time
must also be taken into account.
EQUATION 7-1:
CALCULATING OUTPUT
VOLTAGE (VOUT
)
VOUT = VZS + (N * VS)
When RFS = RZS = 0 : VZS = 0V
FS = VREF
V
7.1
Output Buffer / V
Operation
OUT
VZS is the VOUT voltage when the wiper code = 00h.
The DAC output is buffered with a low power and
precision output amplifier (op amp). This amplifier
provides a rail-to-rail output with low offset voltage and
low noise. The amplifier’s output can drive the resistive
and capacitive loads without oscillation. The amplifier
provides a maximum load current which is enough for
most programmable voltage reference applications.
Figure 7-1 shows a block diagram.
N = wiper code = 0 to 64;
The Serial Shift Register’s value will be latched on the
falling edge of the acknowledge pulse of the write
command’s last byte. Then the VOUT voltage will start
driving to the new value.
The following events update the analog voltage output
(VOUT):
Note 1: The load resistance must stay higher than
5 k for the stable and expected analog
output (to meet electrical specifications).
Refer to:
• Power-On-Reset.
• Falling edge of the acknowledge pulse of the last
write command byte.
•
Section 1.0 “Electrical Charac-
teristics” for the specifications of
the output amplifier.
7.1.2
STEP VOLTAGE (VS)
The Step voltage is dependent on the device resolution
(64 RS) and the output voltage range (VZS to VFS).
Equation 7-2 shows the calculation for the step resis-
tance.
•
Section 7.3 “Driving Resistive
and Capacitive Loads” for addi-
tional design information.
EQUATION 7-2:
VS CALCULATION
Gain =1x
(VFS - VZS
)
VS =
64
Op
VFS is the VOUT voltage when the wiper code is at
full-scale.
VOUT
Amp
VW
VZS is the VOUT voltage when the wiper code is at
zero-scale.
FIGURE 7-1:
Output Buffer Block
Diagram.
Table 7-1 shows the calculated VOUT voltages for the
given volatile Wiper Register value. These calculations
are based on different VREF voltage values (1.5V, 3.3V,
and 5.0V) with an assumption that RFS = RZS = 0 .
2012 Microchip Technology Inc.
DS25154A-page 41
MCP47A1
TABLE 7-1:
Wiper Value
THEORETICAL DAC OUTPUT VALUES
VOUT ( 1)
VREF
3.3
VOUT ( 1)
VREF
3.3
Wiper Value
Ratio
Ratio
Hex
Dec
1.5
5.0
Hex
Dec
1.5
5.0
00h
01h
02h
03h
04h
05h
06h
07h
08h
09h
0Ah
0Bh
0Ch
0Dh
0Eh
0Fh
10h
11h
12h
13h
14h
15h
16h
17h
18h
19h
1Ah
1Bh
1Ch
1Dh
1Eh
1Fh
0
0.0000 0.0000 0.0000 0.0000
0.0156 0.0234 0.0516 0.0781
0.0313 0.0469 0.1031 0.1563
0.0469 0.0703 0.1547 0.2344
0.0625 0.0938 0.2063 0.3125
0.0781 0.1172 0.2578 0.3906
0.0938 0.1406 0.3094 0.4688
0.1094 0.1641 0.3609 0.5469
0.1250 0.1875 0.4125 0.6250
0.1406 0.2109 0.4641 0.7031
0.1563 0.2344 0.5156 0.7813
0.1719 0.2578 0.5672 0.8594
0.1875 0.2813 0.6188 0.9375
0.2031 0.3047 0.6703 1.0156
0.2188 0.3281 0.7219 1.0938
0.2344 0.3516 0.7734 1.1719
0.2500 0.3575 0.8250 1.2500
0.2656 0.3984 0.8766 1.3281
0.2813 0.4219 0.9281 1.4063
0.2969 0.4453 0.9797 1.4844
0.3125 0.4688 1.0313 1.5625
0.3281 0.4922 1.0828 1.6406
0.3438 0.5156 1.1344 1.7188
0.3594 0.5391 1.1859 1.7969
0.3750 0.5625 1.2375 1.8750
0.3906 0.5859 1.2891 1.9531
0.4063 0.6094 1.3406 2.0313
0.4219 0.6328 1.3922 2.1094
0.4375 0.6563 1.4438 2.1875
0.4531 0.6797 1.4953 2.2656
0.4688 0.7031 1.5469 2.3438
0.4844 0.7266 1.5984 2.4219
20h
21h
22h
23h
24h
25h
26h
27h
28h
29h
2Ah
2Bh
2Ch
2Dh
2Eh
2Fh
30h
31h
32h
33h
34h
35h
36h
37h
38h
39h
3Ah
3Bh
3Ch
3Dh
3Eh
3Fh
40h
32
33
34
35
36
37
38
39
40
41
42
43
44
45
46
47
48
49
50
51
52
53
54
55
56
57
58
59
60
61
62
63
64
0.5000
0.5156
0.5313
0.5469
0.5625
0.5781
0.5938
0.6094
0.6250
0.6406
0.6563
0.6719
0.6875
0.7031
0.7188
0.7344
0.7500
0.7656
0.7813
0.7969
0.8125
0.8281
0.8438
0.8594
0.8750
0.8906
0.9063
0.9219
0.9375
0.9531
0.9688
0.9844
1.0000
0.7500 1.6500 2.5000
0.7734 1.7016 2.5781
0.7969 1.7531 2.6563
0.8203 1.8047 2.7344
0.8438 1.8563 2.8125
0.8672 1.9078 2.8906
0.8906 1.9594 2.9688
0.9141 2.0109 3.0469
0.9375 2.0625 3.1250
0.9609 2.1141 3.2031
0.9844 2.1656 3.2813
1.0078 2.2172 3.3594
1.0313 2.2688 3.4375
1.0547 2.3203 3.5156
1.0781 2.3719 3.5938
1.1016 2.4234 3.6719
1.1250 2.4750 3.7500
1.1484 2.5266 3.8281
1.1719 2.5781 3.9063
1.1953 2.6297 3.9844
1.2188 2.6813 4.0625
1.2422 2.7328 4.1406
1.2656 2.7844 4.2188
1.2891 2.8359 4.2969
1.3125 2.8875 4.3750
1.3359 2.9391 4.4531
1.3594 2.9906 4.5313
1.3828 3.0422 4.6094
1.4063 3.0938 4.6875
1.4297 3.1453 4.7656
1.4531 3.1969 4.8438
1.4766 3.2484 4.9219
1.5000 3.3000 5.0000
1
2
3
4
5
6
7
8
9
10
11
12
13
14
15
16
17
18
19
20
21
22
23
24
25
26
27
28
29
30
31
Note 1:
VOUT voltages based on RFS and RZS = 0 .
DS25154A-page 42
2012 Microchip Technology Inc.
MCP47A1
Figure 7-3 shows the equations for solving for VOUT
voltage, the VREF voltage, or the maximum DAC
Register code, based on knowing the requirements for
two of these variables. For VDD voltages below the
specified analog performance voltage (2.7V), the
calibration of the device could be done to ensure VOUT
voltage is not driven into the output amplifier nonlinear
region via the DAC Register value / VREF voltage.
Using the measured VNL voltage as the VOUT voltage
will allow you to balance your selection of the VREF
voltage and maximum DAC Code. The DAC Register
code of 64 is the full-scale code.
7.1.3
AMPLIFIER INPUT VOLTAGE (VW)
To ensure that the amplifier is operating in its linear
range, the voltage (VW) into the output amplifier’s input
has requirements that must be met.
For device VDD voltages 2.7V, the amplifier is in the
linear region for all VREF voltages ( 1.0V) and DAC
register codes.
For device VDD voltages < 2.7V, there will be a voltage
where the amplifier output is no longer linear with the
amplifier input voltage (VW). This is shown in Figure 2-
20, where VDD = 1.8V and the VREF = 1.6V. Higher
DAC register codes are the first to encounter the
nonlinearity of the output buffer. The nonlinearity is also
influenced by the temperature of operation.
DAC Code
VOUT = VREF
*
64
Figure 7-2 shows the trend of the amplifier linearity
based on the device VDD / VREF voltages and the input
voltage to the amplifier. The trend will also be affected
by device temperature. VNL is the voltage where the
amplifier’s output becomes nonlinear. While the VW
voltage is less than the VNL voltage, the amplifier’s out-
put is linear. Once the device VDD has been lowered to
where the amplifier’s nonlinear range increases, the
two methods to keep VW < VNL are:
64 * VOUT
DAC Code
VREF
=
64 * VOUT
DAC Code =
VREF
FIGURE 7-3:
DAC Register Code.
Solving for VOUT, VREF, or
1. Lower the VREF voltage
2. Decrease the DAC Register code
Both methods reduce the maximum usable output
voltage.
VDD
VREF
/
VDD = 5.5V
VDD = 1.8V
VW
Ideal
Actual
(Based on device
VDD and temperature)
0
VDD / VREF
VOUT
FIGURE 7-2:
Amplifier Input (VW) to
Amplifier Output (VOUT) General Characteristics
(VREF = VDD).
2012 Microchip Technology Inc.
DS25154A-page 43
MCP47A1
7.2
Output Slew Rate
7.3
Driving Resistive and Capacitive
Loads
Figure 7-4 shows an example of the slew rate of the
VOUT pin. The slew rate can be affected by the
characteristics of the circuit connected to the VOUT pin.
The VOUT pin can drive up to 100 pF of capacitive load
in parallel with a 5 k resistive load (to meet electrical
specifications). Figure 2-29 shows the VOUT vs.
Resistive Load.
VOUT(B)
VOUT drops slowly as the load resistance decreases
after about 3.5 k . It is recommended to use a load
with RL greater than 5 k.
Driving large capacitive loads can cause stability
problems for voltage feedback op amps. As the load
capacitance increases, the feedback loop’s phase
margin decreases and the closed-loop bandwidth is
reduced. This produces gain peaking in the frequency
response with overshoot and ringing in the step
response. That is, since the VOUT pin’s voltage does
not quickly follow the buffer’s input voltage (due to the
large capacitive load), the output buffer will overshoot
the desired target voltage. Once the driver detects this
overshoot, it compensates by forcing it to a voltage
below the target. This causes voltage ringing on the
VOUT pin.
VOUT(A)
Wiper = A
Wiper = B
Time
| VOUT(B) - VOUT(A)
|
Slew Rate =
T
FIGURE 7-4:
VOUT Pin Slew Rate.
7.2.1
SMALL CAPACITIVE LOAD
With a small capacitive load, the output buffer’s current
is not affected by the capacitive load (CL). But still, the
VOUT pin’s voltage is not a step transition from one
output value (wiper code value) to the next output
value. The change of the VOUT voltage is limited by the
output buffer’s characteristics, so the VOUT pin voltage
will have a slope from the old voltage to the new
voltage. This slope is fixed for the output buffer, and is
referred to as the buffer slew rate (SRBUF).
So, when driving large capacitive loads with the output
buffer, a small series resistor (RISO) at the output (see
Figure 7-5) improves the output buffer’s stability (feed-
back loop’s phase margin) by making the output load
resistive at higher frequencies. The bandwidth will be
generally lower than the bandwidth with no capacitive
load.
7.2.2
LARGE CAPACITIVE LOAD
VOUT
VCL
CL
Op
Amp
VW
With a larger capacitive load, the slew rate is deter-
mined by two factors:
RISO
RL
• The output buffer’s short circuit current (ISC
• The VOUT pin’s external load
)
IOUT cannot exceed the output buffer’s short circuit
current (ISC), which fixes the output buffer slew rate
FIGURE 7-5:
Buffer for Large Capacitive Loads (CL).
Circuit to Stabilize Output
(SRBUF). The voltage on the capacitive load (CL), VCL
,
The RISO resistor value for your circuit needs to be
selected. The resulting frequency response peaking
and step response overshoot for this RISO resistor
value should be verified on the bench. Modify the
changes at a rate proportional to IOUT, which fixes a
capacitive load slew rate (SRCL).
So the VCL voltage slew rate is limited to the slower of
the output buffer’s internally set slew rate (SRBUF) and
the capacitive load slew rate (SRCL).
RISO’s resistance value until the output characteristics
meet your requirements.
A method to evaluate the system’s performance is to
inject a step voltage on the VREF pin and observe the
VOUT pin’s characteristics.
Note:
Additional insight into circuit design for
driving capacitive loads can be found in
AN884 “Driving Capacitive Loads With Op
Amps” (DS00884).
DS25154A-page 44
2012 Microchip Technology Inc.
MCP47A1
TABLE 7-2:
CALCULATION COMPARISON
7.4
Output Errors
Example Theoretical
Delta
The output error is caused by two factors. These are:
RVREF
RFS
20,180
—
• Characteristics of the Resistor Network
• Characteristics of the Output Buffer
100
80
0
0
100
80
RZS
Figure 7-6 shows the components of the error on the
output voltage. The first part of the error is from the
resistor ladder and the RFS and RZS resistances. The
second part is due to the output buffer’s input offset
characteristics.
R1 + 64*RS +
R2
30,000
30,180
- 180
R1, RAB, R2
VREF
VFS
10,000
10,060
- 60
—
5.00 V
The RFS and RZS resistances affect the voltage
between VZS and VFS. The larger that RFS + RZS is, the
smaller that the step voltage (VS) will be (from the
theoretical step voltage). The increase in the RFS and
RZS resistances also effects the Full Scale Error (FSE),
Zero Scale Error (ZSE), and gain error.
3.3267 V
1.6700 V
3.3333 V
1.6667 V
- 6.6 mV
+ 3.3 mV
VZS
VS
25.88 mV 26.04 mV - 0.16 mV
VREF
VFS
1.5V
1.0000 V
0.5000 V
—
0.9980 V
0.5010 V
- 2.0 mV
+ 1.0 mV
Table 7-2 compares theoretical resistor network volt-
ages for full scale and zero scale, where RFS = RZS
VZS
=
VS
7.766 mV 7.813 mV -0.047mV
0 , to an example where RFS and RZS and non-zero.
The voltage calculations show cases of VREF = 5.0V
and VREF = 1.5V. Figure 2-34 shows RVREF, RFS, and
Note 1: RVREF = R1 + RAB + R2 ,
RAB = RFS + 64*RS + RZS
VS = (VFS - VZS) / 64
.
RZS resistances VDD
.
So, as the voltage reference (VREF) decreases, the
Step voltages (VS) decrease. At a low VREF voltage, the
step voltage approaches the magnitude of the output
buffer’s input offset voltage (design target of ± 4.5 mV).
So, for low VREF voltages, the output buffer errors have
greater influence on the VOUT voltage.
Theoretical VFS ( VREF
)
( RFS 0 )
VREF
VOUT(FS)
VFS-RL
Variations due to Output Buffer’s
Input Offset voltage and Buffer’s Impedance / Load
(Due to RFS 0)
VZS-RL
(Due to RZS 0)
(VFS - VZS
)
Step Voltage (VS) =
When:
* VREF
64
VOUT(ZS)
VSS
R
FS = RZS = 0 .
VS = VREF / 64
VREF
2.7V
Theoretical VZS ( VSS
( RZS 0 )
)
5.0V
1.8V
1.5V
1.0V
VS 78.125mV 42.19mV 28.13mV 23.44mV 15.63mV
when RFS = RZS = 0 .
FIGURE 7-6:
Output Voltage (VOUT) Error.
2012 Microchip Technology Inc.
DS25154A-page 45
MCP47A1
NOTES:
DS25154A-page 46
2012 Microchip Technology Inc.
MCP47A1
8.1
DC Set Point or Calibration
8.0
APPLICATIONS EXAMPLES
A
common application for the devices is
a
The MCP47A1 family of devices are general purpose,
single-channel voltage output DACs for various
applications where a precision operation with low
power is needed.
digitally-controlled set point and/or calibration of
variable parameters, such as sensor offset or slope.
For example, the MCP47A1 provides 64 output steps
over the voltage reference range. If voltage reference is
1.65V, the LSb size is 1.65V / 64, or ~ 25.78 mV.
The MCP47A1 devices are rail-to-rail output DACs
designed to operate with a VDD range of 1.8V to 5.5V.
The internal output op amplifier is robust enough to
drive common, small-signal loads directly, thus
eliminating the cost and size of external buffers for
most applications.
Applications that need accurate detection of an input
threshold event often need several sources of error
eliminated. Use of comparators and operational
amplifiers (op amps) with low offset and gain error can
help achieve the desired accuracy, but in many
applications, the input source variation is beyond the
designer’s control. If the entire system can be
calibrated after assembly in a controlled environment
(like factory test), these sources of error are minimized,
if not entirely eliminated. Figure 8-1 illustrates this
example circuit. Equation 8-1 shows a quick estimation
Applications generally suited for the devices are:
• Set Point or Offset Trimming
• Sensor Calibration
• Portable Instrumentation (Battery Powered)
• Motor Control
Application examples include:
of the wiper value given the desired voltage trip (VTRIP
point.
)
• DC Set Point or Calibration
• Decreasing Output Step Size
• Building a “Window” DAC
VREF VDD
MCP47A1
VCC
+
• Selectable Gain and Offset Bipolar Voltage
Output
VO
VSENSE
Comp.
• Building Programmable Current Source
• Serial Interface Communication Times
• Software I2C Interface Reset Sequence
VTRIP
C1
VOUT
VCC
–
I2C™
In the design of a system with the MCP47A1 devices,
the following considerations should be taken into
account:
2-wire
FIGURE 8-1:
Calibration.
Set Point or Threshold
• Power Supply Considerations (Noise)
• PCB Area Requirements
EQUATION 8-1:
ESTIMATING THE WIPER
VALUE (N) FROM THE
DESIRED VTRIP
• Connecting to I2C BUS using Pull-Up
Resistors
VTRIP = VOUT = (N * VS)
( VTRIP - VREF
VS
)
N =
Where: VS = VREF / 64
Note: Calculation does not take into account RFS
and RZS resistors of the DAC’s resistor ladder (see
Section 7.1 for additional information).
2012 Microchip Technology Inc.
DS25154A-page 47
MCP47A1
8.1.1
DECREASING OUTPUT STEP SIZE
8.1.2
BUILDING A “WINDOW” DAC
Due to the step voltage and output range of the
MCP47A1, it may be desirable to reduce the step
voltage while also modifying the range of the output. A
common method to achieve this smaller step size is a
voltage divider on the DAC’s output. Figure 8-2
illustrates this concept. Equation 8-2 shows a quick
estimation of the wiper value given the desired voltage
trip (VTRIP) point.
When calibrating a set point or threshold of a sensor,
typically only a small portion of the DAC output range is
utilized. If the LSb size is adequate enough to meet the
application’s accuracy needs, the unused range is
sacrificed without consequences. If greater accuracy is
needed, then the output range will need to be reduced
to increase the resolution around the desired threshold.
If the threshold is not near VREF, 2 • VREF, or VSS then
creating a “window” around the threshold has several
advantages. One simple method to create this
“window” is to use a voltage divider network with a
pull-up and pull-down resistor. Figure 8-3 and Figure 8-
4 illustrate this concept.
For example, if R1 = R2, then the VTRIP voltage range
is from VSS to 1/2 * VREF. Also at the VTRIP node, the
step voltage is 1/2 the step voltage at the VOUT node.
A bypass capacitor on the output of the voltage divider
plays a critical function in attenuating the output noise
of the DAC and the induced noise from the
environment.
VCC+
VREF VDD
RSENSE
VCC
+
VREF VDD
MCP47A1
VCC+
VO
VSENSE
R1
VOUT
Comp.
R3
R2
VO
R1
MCP47A1
VTRIP
Comp.
VTRIP
C1
R2
VCC
–
VOUT
C1
I2C™
VCC–
2-wire
I2C™
2-wire
VCC–
FIGURE 8-2:
Example Circuit Of Set Point
or Threshold Calibration.
FIGURE 8-3:
Single-Supply “Window”
DAC.
EQUATION 8-2:
VOUT AND VTRIP
ESTIMATIONS
EQUATION 8-3:
V
OUT AND VTRIP
ESTIMATIONS
VOUT = N * VS
VS = VREF / 64
VOUT = N * VS
VS = VREF / 64
R2
R1 + R2
VTRIP = VOUT
*
VOUT * R23 + V23 * R1
R1 + R23
VTRIP
=
Note:
The VOUT voltage can also be scaled by a
resistor from the VREF pin to the system
reference voltage. Care should be taken
with this implementation due to the ± 20%
variation to the 20k typical resistance
from the VREF pin to ground (RVREF). This
variation in resistance directly effects the
actual VOUT voltage.
R2 * R3
R2 + R3
R23
V23
=
=
Thevenin
Equivalent
(VCC+ * R2) * (VCC- * R3)
R2 + R3
R1
VOUT
VTRIP
R23
V23
DS25154A-page 48
2012 Microchip Technology Inc.
MCP47A1
EQUATION 8-4:
GAIN CALCULATION
8.2
Selectable Gain and Offset Bipolar
Voltage Output
R2
Gain =
R1
In some applications, control of the output range is
desirable. Figure 8-4 shows a circuit using a DAC
device to achieve a bipolar or single-supply application.
This circuit is typically used for linearizing a sensor
whose slope and offset varies. Depending on the out-
put range desired, resistor R4 or resistor R5 may not be
required. Equation 8-4 shows the calculation of the
Gain, while Equation 8-5 shows the calculation of the
VO voltage.
If desired Gain = 0.5, and R1 is selected as 20 k
then R2 would need to be 10 k .
EQUATION 8-5:
BIPOLAR “WINDOW” DAC
CALCULATIONS
R2
R1
R2
R1
VO = VOA+ • ( 1 +
) - VIN • (
)
This circuit can be simplified if the window range is
limited (by removing either the R4 or R5 resistor).
Figure 8-5 shows a circuit for the case where the R5
resistor is removed. Resistors R1 and R2 control the
gain, while resistors R3 and R4 shift the DAC's output
to a selected offset. Equation 8-6 shows the calculation
of the VO voltage.
Offset Adjust
Gain Adjust
(VOUT • R45) + (V45 • R3)
R3 + R45
VOA+
=
=
(VCC+ • R4) + (VCC- • R5)
R4 + R5
V45
Note:
R4 can be tied to VDD, instead of VSS, if a
higher offset is desired.
R4 • R5
R45
=
R4 + R5
VCC
+
(1)
VOUT = N * VS
VREF VDD
MCP47A1
VCC
+
R5
VREF
R3
VOUT
VOA+
C1
VS =
VO
192
R4
Note 1: VOUT calculation does not take into
account RFS and RZS resistors of the DAC’s
resistor ladder (see Section 7.1 for additional
information).
VCC–
I2C™
2-wire
V
–
CC
R2
VIN
R1
Note: Capacitor C1 is recommended (0.1uF typical)
EQUATION 8-6:
SIMPLIFIED BIPOLAR
“WINDOW” DAC
CALCULATIONS
FIGURE 8-4:
Selectable Gain and Offset Circuit.
Bipolar Voltage Source with
R2
R1
R2
R1
VO = VOA+ • ( 1 +
) - VIN • (
)
VREF VDD
R4
VOA+ = VOUT • (
)
VCC
+
R3 + R4
R3
VOA+
VO
MCP47A1
VOUT = N * VS
VOUT
C1
R4
Note 1: VOUT calculation does not take into
account RFS and RZS resistors of the DAC’s
resistor ladder (see Section 7.1 for additional
information).
VCC
–
I2C™
2-wire
R2
VIN
R1
Note: Capacitor C1 is recommended (0.1uF typical)
FIGURE 8-5: Simplified Bipolar Voltage
Source with Selectable Gain and Offset Circuit.
2012 Microchip Technology Inc.
DS25154A-page 49
MCP47A1
8.3
Building Programmable Current
Source
8.4
Serial Interface Communication
Times
Figure 8-6 shows an example of building
a
Table 8-1 shows time for each I2C serial interface
command as well as the effective data update rate that
can be supported by the digital interface (based on the
two I2C serial interface frequencies). The continuous
write command allows a higher data update frequency
since for the fixed overhead more bytes are
transferred. The Serial Interface performance, along
with the VOUT output performance (such as slew rate),
would be used to determine the application’s volatile
DAC register update rate.
programmable current source using a voltage follower.
The current sensor resistor is used to convert the DAC
voltage output into a digitally-selectable current source.
The smaller RSENSE is, the less power is dissipated
across it. However, this also reduces the resolution that
the current can be controlled.
VDD
(or VREF
)
VREF VDD
MCP47A1
Load
VCC
+
VOUT
IL
Ib
I2C™
VCC–
2-wire
IL
RSENSE
Ib = ----
VOUT
IL = -------------- ------------
Rsense + 1
where Common-Emitter Current Gain
FIGURE 8-6:
Digitally-Controlled Current
Source.
TABLE 8-1:
SERIAL INTERFACE TIMES / FREQUENCIES
Example
Command
Time (µs)
Effective Data Update
Frequency (kHz) (2)
# of Serial
# Bytes
# of Serial
Interface bits(1) Transferred Interface bits 100kHz 400kHz
100kHz
3.4
400kHz
13.8
Command
Write Single Byte
Write Continuous Bytes
Read Byte
29
20 + N * 9
39
1
5
1
29
65
39
290.0
650.0
390.0
72.5
162.5
97.5
7.7
30.8
2.6
10.3
Note 1: Includes the Start or Stop bits.
2: This is the command frequency multiplied by the number of bytes transferred.
DS25154A-page 50
2012 Microchip Technology Inc.
MCP47A1
2
The nine bits of ‘1’ are used to force a Reset of those
devices that could not be reset by the previous Start bit.
This occurs only if the MCP47A1 is driving an Abit on
the I2C bus, or is in output mode (from a Read
command) and is driving a data bit of ‘0’ onto the I2C
bus. In both of these cases, the previous Start bit could
not be generated due to the MCP47A1 holding the bus
low. By sending out nine ‘1’ bits, it is ensured that the
device will see an A bit (the Master Device does not
drive the I2C bus low to acknowledge the data sent by
the MCP47A1), which also forces the MCP47A1 to
reset.
8.5
Software I C Interface Reset
Sequence
Note:
This technique should be supported by
any I2C compliant device. The 24XXXX
I2C Serial EEPROM devices support this
technique, which is documented in
AN1028.
At times, it may become necessary to perform a
Software Reset Sequence to ensure the MCP47A1
device is in a correct and known I2C Interface state.
This technique only resets the I2C state machine.
The 2nd Start bit is sent to address the rare possibility
of an erroneous write. This could occur if the Master
Device was reset while sending a Write command to
the MCP47A1, AND then as the Master Device returns
to normal operation and issues a Start condition, while
the MCP47A1 is issuing an Acknowledge. In this case,
if the 2nd Start bit is not sent (and the Stop bit was sent)
the MCP47A1 could initiate a write cycle.
This is useful if the MCP47A1 device powers up in an
incorrect state (due to excessive bus noise, etc), or if
the Master Device is reset during communication.
Figure 8-7 shows the communication sequence to
software reset the device.
S
‘1’ ‘1’ ‘1’ ‘1’ ‘1’ ‘1’ ‘1’ ‘1’
S
P
Nine bits of ‘1’
Start bit
Note:
The potential for this erroneous write
ONLY occurs if the Master Device is reset
while sending a Write command to the
MCP47A1.
Start
bit
Stop bit
FIGURE 8-7:
Format.
Software Reset Sequence
The Stop bit terminates the current I2C bus activity. The
MCP47A1 waits to detect the next Start condition.
The 1st Start bit will cause the device to reset from a
state in which it is expecting to receive data from the
Master Device. In this mode, the device is monitoring
the data bus in Receive mode and can detect if the
Start bit forces an internal Reset.
This sequence does not effect any other I2C devices
which may be on the bus, as they should disregard this
as an invalid command.
2012 Microchip Technology Inc.
DS25154A-page 51
MCP47A1
8.6
Design Considerations
VDD
VDD
8.6.1
POWER SUPPLY
CONSIDERATIONS (NOISE)
0.1 µF
0.1 µF
Inductively-coupled AC transients and digital switching
noise can degrade the input and output signal integrity,
potentially masking the MCP47A1’s performance.
Careful board layout minimizes these effects and
increases the Signal-to-Noise Ratio (SNR). Multi-layer
SCL
SDA
VREF
VOUT
boards utilizing
a low-inductance ground plane,
isolated inputs, isolated outputs and proper decoupling
are suggested. Particularly harsh environments may
require shielding of critical signals.
The device’s power sources (VDD and VREF) should be
as clean as possible. Any noise induced on the VDD
and VREF signals can affect the DAC performance.
Separate digital and analog ground planes are
recommended.
VSS
VSS
FIGURE 8-8:
Connections.
Typical Microcontroller
Typical applications require a bypass capacitor in order
to filter high-frequency noise on the VDD and VREF sig-
nals. The noise can be induced onto the power supply’s
traces or as a result of changes on the DAC output. The
bypass capacitor helps to minimize the effect of these
noise sources on signal integrity. Figure 8-8 illustrates
an appropriate bypass strategy.
Optional
V
REF
Analog
Optional
C3
C4 C5
Output
V
C1 C2
VDD
6 VREF
1
2
5
In this example, the recommended bypass capacitor
value is 0.1 µF. This capacitor should be placed as
close to the device power pin (VDD) as possible (within
4 mm).
DD
VSS
VOUT
SDA
4
R1
R2
SCL 3
To MCU
Separate digital and analog ground planes are
recommended. In this case, the VSS pin and the ground
pins of the VDD capacitors should be terminated to the
analog ground plane and VDD and VSS should reside
on the analog plane.
2
R1 and R2 are I C pull-up resistors:
R1 and R2:
5 k - 10 k for f
=
100 kHz to 400 kHz
Ceramic
SCL
Figure 8-9 shows an example of using two bypass
capacitors (a 10 µF tantalum capacitor and a 0.1 µF
ceramic capacitor) in parallel on the VDD line. These
capacitors should be placed as close to the VDD pin as
possible (within 4 mm). If the application circuit has
separate digital and analog power supplies, the VDD
and VSS pins of the device should reside on the analog
plane.
C1: 0.1 µF capacitor
C2: 10 µF capacitor
C3: ~ 0.1 µF
Tantalum
Optional to reduce noise
in V pin.
OUT
C4: 0.1 µF capacitor
C5: 10 µF capacitor
Ceramic
Tantalum
FIGURE 8-9:
Example MCP47A1 Circuit.
Note:
Breadboards and wire-wrapped boards
are not recommended.
DS25154A-page 52
2012 Microchip Technology Inc.
MCP47A1
8.6.2
PCB AREA REQUIREMENTS
8.6.4
CONNECTING TO I2C BUS USING
PULL-UP RESISTORS
In some applications, PCB area is a criteria for device
selection. Table 8-2 shows the typical package
dimensions and area for the different package options.
The SCL and SDA pins of the MCP47A1 devices are
open-drain configurations. These pins require a pull-up
resistor as shown in Figure 8-9.
TABLE 8-2:
Package
PACKAGE FOOTPRINT (1)
Package Footprint
The pull-up resistor values (R1 and R2) for SCL and
SDA pins depend on the operating speed (standard,
fast, and high speed) and loading capacitance of the
I2C bus line. A higher value of the pull-up resistor
consumes less power, but increases the signal
transition time (higher RC time constant) on the bus
line. Therefore, it can limit the bus operating speed.
The lower resistor value, on the other hand, consumes
higher power, but allows higher operating speed. If the
bus line has higher capacitance due to long metal
traces or multiple device connections to the bus line, a
smaller pull-up resistor is needed to compensate the
long RC time constant. The pull-up resistor is typically
chosen between 1 kand 10 kranges for standard
and fast modes.
Dimensions (mm)
Type
Code
Length
Width
6
SC70
LT
3.10
3.20
9.92
Note 1: Does not include recommended Land
Pattern dimensions. Dimensions are Max
values.
8.6.3
PINOUT/FOOTPRINT
COMPATIBILITY
The MCP47A1 has a pinout and footprint compatibility
to the MCP40D18 and MCP4018 devices.
8.6.4.1
Device Connection Test
The user can test the presence of the device on the I2C
bus line using a simple I2C command. This test can be
achieved by checking an acknowledge response from
the device after sending a read or write command.
Figure 8-10 shows an example with a read command.
The steps are:
The MCP40D18/MCP4018’s W pin is analogous to the
MCP47A1’s VOUT pin, while the MCP40D18/
MCP4018’s A pin is analogous to the MCP47A1’s VREF
pin. The MCP40D18 and MCP47A1 share the same
I2C command protocol structure.
a) Set the R/W bit “High” in the device’s address
byte.
b) Check the ACK bit of the address byte.
If the device acknowledges (ACK = 0) the
command, then the device is connected,
otherwise it is not connected.
c) Send Stop bit.
Address Byte
SCL
SDA
1
1
2
1
3
0
4
1
5
6
7
8
1
9
A2 A1 A0
Start
Bit
Stop
Bit
Address bits
Device Code
R/W
Device
Response
FIGURE 8-10:
I2C Bus Connection Test.
2012 Microchip Technology Inc.
DS25154A-page 53
MCP47A1
NOTES:
DS25154A-page 54
2012 Microchip Technology Inc.
MCP47A1
9.0
9.1
DEVELOPMENT SUPPORT
Note:
Since the SC70EV is a generic board, the
noise immunity of the board will not be
optimal. If noise immunity is a require-
ment, then a you will need to develop a
custom PCB for the MCP47A1. This PCB
would need to use good layout techniques
to reduce noise coupling.
Evaluation/Demonstration Boards
The MCP47A1 devices do not have a dedicated
evaluation or demonstration board. Figure 9-1 shows
the component connections to make an evaluation
board using the SC70EV Bond Out PCB (order #
SC70EV). This will allow the MCP47A1’s capabilities to
be evaluated with the PICkit™ Serial Analyzer (order #
DV164122).
0
1.0 µF
0.1 µF
(1)
VDD
V
REF
VSS
V
OUT
0
CL & RL
4.7 k
4.7 k
SCL
SDA
Required components
Recommended components for noise filtering
Optional I2C bus pull up resistors (value may need to be adjusted for your system)
Optional VOUT loading components (stacked), CL = 1 nF max and RL = 5 k max
Note 1: The VREF pin (P8) will need to be connected to a reference voltage source (such as VDD).
FIGURE 9-1:
SC70EV Bond Out PCB – Top Layer and Silk-Screen.
2012 Microchip Technology Inc.
DS25154A-page 55
MCP47A1
9.2
Technical Documentation
Several additional technical documents are available to
assist you in your design and development. These
technical documents include Application Notes,
Technical Briefs, and Design Guides. Table 9-1 shows
some of these documents.
TABLE 9-1:
TECHNICAL DOCUMENTATION
Title
Application
Literature #
Note Number
AN1326
Using DAC for LDMOS Amplifier Bias Control Applications
Signal Chain Design Guide
DS01326
DS21825
DS01005
—
—
Analog Solutions for Automotive Applications Design Guide
DS25154A-page 56
2012 Microchip Technology Inc.
MCP47A1
10.0 PACKAGING INFORMATION
10.1 Package Marking Information
6-Lead SC-70
Example
BANN
Part Number
Code
Part Number
Code
MCP47A1T-A0E/LT
BANN
MCP47A1T-A1E/LT
BCNN
Legend: XX...X Customer-specific information
Y
YY
WW
NNN
Year code (last digit of calendar year)
Year code (last 2 digits of calendar year)
Week code (week of January 1 is week ‘01’)
Alphanumeric traceability code
e
3
Pb-free JEDEC designator for Matte Tin (Sn)
*
This package is Pb-free. The Pb-free JEDEC designator (
can be found on the outer packaging for this package.
)
e3
Note: In the event the full Microchip part number cannot be marked on one line, it will
be carried over to the next line, thus limiting the number of available
characters for customer-specific information.
2012 Microchip Technology Inc.
DS25154A-page 57
MCP47A1
Note: For the most current package drawings, please see the Microchip Packaging Specification located at
http://www.microchip.com/packaging
DS25154A-page 58
2012 Microchip Technology Inc.
MCP47A1
Note: For the most current package drawings, please see the Microchip Packaging Specification located at
http://www.microchip.com/packaging
2012 Microchip Technology Inc.
DS25154A-page 59
MCP47A1
Note: For the most current package drawings, please see the Microchip Packaging Specification located at
http://www.microchip.com/packaging
DS25154A-page 60
2012 Microchip Technology Inc.
MCP47A1
APPENDIX A: REVISION HISTORY
Revision A (August 2012)
• Original Release of this Document.
2012 Microchip Technology Inc.
DS25154A-page 61
MCP47A1
B.4
Full-Scale Error (FSE)
APPENDIX B: TERMINOLOGY
The Full-Scale Error (FSE) is the difference between
the ideal and measured DAC output voltage with the
Wiper’s position set to its maximum (Wiper code =
40h); see Figure B-3. Full-scale error may also be
thought of as the sum of the offset error plus gain error.
B.1
Resolution
The resolution is the number of DAC output states that
divide the full-scale range. For the 6-bit DAC, the
resolution is 26, meaning the DAC code ranges from 0
to 64.
See Figure 2-9 through Figure 2-12 for FSE
characterization graphs.
B.2
Least Significant Bit (LSb)
EQUATION B-2:
FULL SCALE ERROR
Normally, this is thought of as the ideal voltage
difference between two successive codes. This bit has
the smallest value or weight of all bits in the register.
V
- V
OUT(@FS)
IDEAL(@FS)
FSE =
V
LSb
For a given output voltage range, which is typically the
voltage between the Full-Scale voltage and the Zero-
Scale voltage (VOUT(FS) - VOUT(ZS)), it is divided by the
resolution of the device (Equation B-1).
Where:
FSE is expressed in LSb
V
V
V
is the V
register code is at Full-scale.
voltage when the DAC
OUT
OUT(@FS)
is the ideal output voltage when the
DAC register code is at Full-scale.
IDEAL(@FS)
EQUATION B-1:
LSb VOLTAGE
CALCULATION
is the delta voltage of one DAC register code
step (such as code 20h to code 21h).
LSb
VOUT(FS) - VOUT(ZS)
2N
VLSb
=
B.5
Zero-Scale Error (ZSE)
2N = 64 (MCP47A1)
The Zero-Scale Error (ZSE) is the difference between
the ideal and measured VOUT voltage with the Wiper
position set to its minimum (Wiper code = 00h); see
Figure B-3. The Zero-Scale Error is the same as the
Offset Error for this case (Wiper code = 00h).
Equation B-3 shows how to calculate the zero scale
error.
B.3
Monotonic Operation
Monotonic operation means that the device’s output
voltage (VOUT) increases with every one code step
(LSb) change (from terminal B to terminal A). The VOUT
voltage (VW voltage) is the sum of all the Step voltages
plus the voltage at Zero-Scale (VZS). The Zero-Scale
voltage is dependent on the resistance between the tap
0 point and the B Terminal.
See Figure 2-13 through Figure 2-16 for ZSE
characterization graphs.
EQUATION B-3:
ZERO SCALE ERROR
V
OUT(@ZS)
VS64
ZSE =
0x40
0x3F
V
LSb
VS63
Where:
FSE is expressed in LSb
V
is the V
register code is at Zero-scale.
voltage when the DAC
OUT
OUT(@ZS)
0x3E
V
is the delta voltage of one DAC register code
step (such as code 20h to code 21h).
LSb
VS3
0x03
VS1
0x02
VS0
0x01
0x00
VW
n = ?
(@ tap)
VW
=
VSn + VZS(@ Tap 0)
n = 0
Voltage (VW ~= VOUT
)
FIGURE B-1:
VW (VOUT).
DS25154A-page 62
2012 Microchip Technology Inc.
MCP47A1
B.6
Total Unadjusted Error
B.9
Gain Error
The Total Unadjusted Error is the difference between
the ideal and measured VOUT voltage. Typically,
calibration of the output voltage is implemented to
improve system performance.
The Gain error (see Figure B-3) is the difference
between the actual full-scale output voltage, from the
ideal output voltage of the DAC transfer curve. The
gain error is calculated after nullifying the offset error,
or full scale error minus the offset error.
Total Unadjusted Error can be calculated, see
Equation B-4.
The gain error indicates how well the slope of the actual
transfer function matches the slope of the ideal transfer
function. The gain error is usually expressed as percent
of full-scale range (% of FSR) or in LSb. The gain error
is not calibrated at the factory and most of the gain error
is contributed by the output buffer (op amp) saturation.
EQUATION B-4:
TOTAL UNADJUSTED
ERROR (LSb)
V
V
REF
V
=
=
* DAC Code
IDEAL
64
REF
Actual Transfer Function
V
LSb
64
Full-Scale
Error
V
- V
MEASURED
IDEAL
Error
=
LSb
V
LSb
Where:
Gain Error
V
is the voltage on the V
pin.
REF
REF
Analog
Output
V
is the V
voltage for the same DAC
OUT
MEASURED
register code as V
is calculated.
IDEAL
Actual Transfer Function
See Figure 2-17 through Figure 2-20 for Total
Unadjusted Error characterization graphs.
after Offset Error is removed
Ideal Transfer Function
Zero-Scale
Error
B.7
Offset Error
0
DAC Input Code
The Offset error (see Figure B-2) is the deviation from
zero voltage output when the volatile DAC Register
value = 00h (zero scale voltage). This error affects all
codes by the same amount. The offset error can be
calibrated by software in application circuits.
FIGURE B-3:
SCALE ERROR EXAMPLE.
GAIN ERROR AND FULL-
B.10 Gain Error Drift
The Gain error drift is the variation in gain error due to
a change in ambient temperature. The gain error drift is
typically expressed in ppm/oC.
Actual Transfer Function
Analog
Output
Ideal Transfer Function
DAC Input Code
Offset
Error
(ZSE)
0
FIGURE B-2:
OFFSET ERROR.
B.8 Offset Error Drift
The Offset error drift is the variation in offset error due
to a change in ambient temperature. The offset error
drift is typically expressed in ppm/oC.
2012 Microchip Technology Inc.
DS25154A-page 63
MCP47A1
B.11 Integral Nonlinearity (INL)
B.12 Differential Nonlinearity (DNL)
The Integral Nonlinearity (INL) error is the maximum
deviation of an actual transfer function from an ideal
transfer function (straight line).
The Differential Nonlinearity (DNL) error (see Figure B-
5) is the measure of step size between codes in actual
transfer function. The ideal step size between codes is
1 LSb. A DNL error of zero would imply that every code
is exactly 1 LSb wide. If the DNL error is less than
1 LSb, the DAC guarantees monotonic output and no
missing codes. The DNL error between any two
adjacent codes is calculated as follows:
In the MCP47A1, INL is calculated using two end
points. The points used are Zero-Scale (00h) and Full-
Scale - 1 (3Fh). INL can be expressed as a percentage
of full scale range (FSR) or in a fraction of an LSb. INL
is also called relative accuracy. Equation B-5 shows
how to calculate the INL error in LSb and Figure B-4
shows an example of INL accuracy.
DNL error is the measure of variations in code widths
from the ideal code width. A DNL error of zero would
imply that every code is exactly 1 LSb wide.
INL error for these devices is the maximum deviation
between an actual code transition point and its
corresponding ideal transition point after offset and
gain errors have been removed. These endpoints are
from 0x00 to 0x40 for the MCP47A1. Refer to Figure B-
4.
See Figure 2-5 through Figure 2-8 for DNL character-
ization graphs.
EQUATION B-6:
DNL ERROR
V
- ( V
- V
)
S
(Code = n)
(Code = n-1)
Positive INL means higher VOUT voltage than ideal.
Negative INL means lower VOUT voltage than ideal.
DNL
=
LSb
V
S
V
- V
ZS
See Figure 2-1 through Figure 2-4 for INL character-
ization graphs.
(Code=63)
V
=
S
63
EQUATION B-5:
INL ERROR
V
- V
IDEAL
OUT
INL
=
LSb
V
S
111
V
= V + ( V * DAC Code )
IDEAL
ZS
S
110
101
100
011
010
001
000
Actual
transfer
function
V
- V
ZS
(Code=63)
V
=
S
63
Wiper
Code
Ideal transfer
function
INL < 0
Wide code, > 1 LSb
111
Actual
transfer
function
110
101
100
Narrow code < 1 LSb
VOUT Output Voltage
Wiper
Code
FIGURE B-5:
DNL ACCURACY.
011
010
001
000
Ideal transfer
function
INL < 0
OUT Output Voltage
INL ACCURACY.
V
FIGURE B-4:
DS25154A-page 64
2012 Microchip Technology Inc.
MCP47A1
B.13 Settling Time
B.16 Power-Supply Rejection Ratio
(PSRR)
The Settling time is the time delay required for the VOUT
voltage to settle into its new output value. This time is
measured from the start of code transition, to when the
PSRR indicates how the output of the DAC is affected
by changes in the supply voltage. PSRR is the ratio of
the change in VOUT to a change in VDD for full-scale
output of the DAC. The VOUT is measured while the
VOUT voltage is within the specified accuracy.
In the MCP47A1, the settling time is a measure of the
time delay until the VOUT voltage reaches within 0.5
LSb of its final value, when the volatile DAC Register
changes from 40h to 50h.
VDD is varied +/- 10%, and expressed in dB or µV/V.
B.17 Ratiometric Temperature
Coefficient
See Figure 2-36 through Figure 2-39 for Settling Time
oscilloscope screen captures.
The ratiometric temperature coefficient quantifies the
error in the ratio of the resistor setting (Resistance from
VREF pin to Wiper position (RVREF-W) and the Wiper
position to Ground (RW-VSS) due to temperature drift.
This error also includes the drift of the output driver
over temperature. This is typically the critical error
when using a DAC.
B.14 Major-Code Transition Glitch
Major-code transition glitch is the impulse energy
injected into the DAC analog output when the code in
the DAC register changes state. It is normally specified
as the area of the glitch in nV-Sec, and is measured
when the digital code is changed by 1 LSb at the major
carry transition (Example: Wiper code changes from
“011111” to “100000”, or from “100000” to
“011111”).
See Figure 2-21 through Figure 2-24 for Tempco
characterization graphs.
B.18 Absolute Temperature Coefficient
The absolute temperature coefficient quantifies the
error in the end-to-end output voltage (Nominal output
voltage VOUT) due to temperature drift. For a DAC, this
error is typically not an issue, due to the ratiometric
aspect of the output.
B.15 Digital Feedthrough
The Digital feedthrough is the glitch that appears at the
analog output caused by coupling from the digital input
pins of the device. The area of the glitch is expressed
in nV-Sec, and is measured with a full scale change
(Example: all 0s to all 1s and vice versa) on the digital
input pins. The digital feedthrough is measured when
the DAC is not being written to the output register.
2012 Microchip Technology Inc.
DS25154A-page 65
MCP47A1
NOTES:
DS25154A-page 66
2012 Microchip Technology Inc.
MCP47A1
PRODUCT IDENTIFICATION SYSTEM
To order or obtain information, e.g., on pricing or delivery, refer to the factory or the listed sales office.
Examples:
PART NO.
Device
XXX
X
/XX
a) MCP47A1T-A0E/LT:
6-bit DAC,
SC70-6,
2
I C Slave Temperature Package
Address Range
Address = 5Ch,
Tape and Reel
6-bit DAC,
2
b) MCP47A1T-A1E/LT:
Device:
MCP47A1T: 6-bit Single DAC with I C interface
(Tape and Reel)
SC70-6,
Address = 7Ch,
Tape and Reel
2
I C Slave Address A0 = 5Ch
A1 = 7Ch
Temperature
Range:
E
= -40°C to +125°C
Package:
LT = Plastic Small Outline Transistor
(SC70), 6-lead
2012 Microchip Technology Inc.
DS25154A-page 67
MCP47A1
NOTES:
DS25154A-page 68
2012 Microchip Technology Inc.
Note the following details of the code protection feature on Microchip devices:
•
Microchip products meet the specification contained in their particular Microchip Data Sheet.
•
Microchip believes that its family of products is one of the most secure families of its kind on the market today, when used in the
intended manner and under normal conditions.
•
There are dishonest and possibly illegal methods used to breach the code protection feature. All of these methods, to our
knowledge, require using the Microchip products in a manner outside the operating specifications contained in Microchip’s Data
Sheets. Most likely, the person doing so is engaged in theft of intellectual property.
•
•
Microchip is willing to work with the customer who is concerned about the integrity of their code.
Neither Microchip nor any other semiconductor manufacturer can guarantee the security of their code. Code protection does not
mean that we are guaranteeing the product as “unbreakable.”
Code protection is constantly evolving. We at Microchip are committed to continuously improving the code protection features of our
products. Attempts to break Microchip’s code protection feature may be a violation of the Digital Millennium Copyright Act. If such acts
allow unauthorized access to your software or other copyrighted work, you may have a right to sue for relief under that Act.
Information contained in this publication regarding device
applications and the like is provided only for your convenience
and may be superseded by updates. It is your responsibility to
ensure that your application meets with your specifications.
MICROCHIP MAKES NO REPRESENTATIONS OR
WARRANTIES OF ANY KIND WHETHER EXPRESS OR
IMPLIED, WRITTEN OR ORAL, STATUTORY OR
OTHERWISE, RELATED TO THE INFORMATION,
INCLUDING BUT NOT LIMITED TO ITS CONDITION,
QUALITY, PERFORMANCE, MERCHANTABILITY OR
FITNESS FOR PURPOSE. Microchip disclaims all liability
arising from this information and its use. Use of Microchip
devices in life support and/or safety applications is entirely at
the buyer’s risk, and the buyer agrees to defend, indemnify and
hold harmless Microchip from any and all damages, claims,
suits, or expenses resulting from such use. No licenses are
conveyed, implicitly or otherwise, under any Microchip
intellectual property rights.
Trademarks
The Microchip name and logo, the Microchip logo, dsPIC,
KEELOQ, KEELOQ logo, MPLAB, PIC, PICmicro, PICSTART,
32
PIC logo, rfPIC and UNI/O are registered trademarks of
Microchip Technology Incorporated in the U.S.A. and other
countries.
FilterLab, Hampshire, HI-TECH C, Linear Active Thermistor,
MXDEV, MXLAB, SEEVAL and The Embedded Control
Solutions Company are registered trademarks of Microchip
Technology Incorporated in the U.S.A.
Analog-for-the-Digital Age, Application Maestro, BodyCom,
chipKIT, chipKIT logo, CodeGuard, dsPICDEM,
dsPICDEM.net, dsPICworks, dsSPEAK, ECAN,
ECONOMONITOR, FanSense, HI-TIDE, In-Circuit Serial
Programming, ICSP, Mindi, MiWi, MPASM, MPLAB Certified
logo, MPLIB, MPLINK, mTouch, Omniscient Code
Generation, PICC, PICC-18, PICDEM, PICDEM.net, PICkit,
PICtail, REAL ICE, rfLAB, Select Mode, Total Endurance,
TSHARC, UniWinDriver, WiperLock and ZENA are
trademarks of Microchip Technology Incorporated in the
U.S.A. and other countries.
SQTP is a service mark of Microchip Technology Incorporated
in the U.S.A.
All other trademarks mentioned herein are property of their
respective companies.
© 2012, Microchip Technology Incorporated, Printed in the
U.S.A., All Rights Reserved.
Printed on recycled paper.
ISBN: 978-1-62076-491-6
QUALITY MANAGEMENT SYSTEM
CERTIFIED BY DNV
Microchip received ISO/TS-16949:2009 certification for its worldwide
headquarters, design and wafer fabrication facilities in Chandler and
Tempe, Arizona; Gresham, Oregon and design centers in California
and India. The Company’s quality system processes and procedures
are for its PIC® MCUs and dsPIC® DSCs, KEELOQ® code hopping
devices, Serial EEPROMs, microperipherals, nonvolatile memory and
analog products. In addition, Microchip’s quality system for the design
and manufacture of development systems is ISO 9001:2000 certified.
== ISO/TS 16949 ==
2012 Microchip Technology Inc.
DS25154A-page 69
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11/29/11
DS25154A-page 70
2012 Microchip Technology Inc.
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