MIC2179BSM-TR [MICROCHIP]
Switching Regulator, Current-mode, 5.5A, 240kHz Switching Freq-Max, PDSO20;型号: | MIC2179BSM-TR |
厂家: | MICROCHIP |
描述: | Switching Regulator, Current-mode, 5.5A, 240kHz Switching Freq-Max, PDSO20 光电二极管 |
文件: | 总13页 (文件大小:353K) |
中文: | 中文翻译 | 下载: | 下载PDF数据表文档文件 |
MIC2179
1.5A Synchronous Buck Regulator
General Description
Features
The Micrel MIC2179 is a 200kHz synchronous buck (step-
down) switching regulator designed for high-efficiency, bat-
tery-powered applications.
• 4.5V to 16.5V input voltage range
• Dual-mode operation for high efficiency (up to 96%)
PWM mode for > 150mA load current
Skip mode for <150mA load current
• 150mΩ internal power MOSFETs at 12V input
• 200kHz preset switching frequency
• Low quiescent current
TheMIC2179operatesfroma4.5Vto16.5Vinputandfeatures
internal power MOSFETs that can supply up to 1.5A output
current. It can operate with a maximum duty cycle of 100%
for use in low-dropout conditions. It also features a shutdown
mode that reduces quiescent current to less than 5µA.
1.0mA in PWM mode
600µA in skip mode
< 5µA in shutdown mode
The MIC2179 achieves high efficiency over a wide output
current range by operating in either PWM or skip mode. The
operating mode is externally selected, typically by an intel-
ligentsystem,whichchoosestheappropriatemodeaccording
to operating conditions, efficiency, and noise requirements.
The switching frequency is preset to 200kHz and can be
synchronized to an external clock signal of up to 300kHz.
• Current-mode control
Simplified loop compensation
Superior line regulation
• 100% duty cycle for low dropout operation
• Current limit
• Thermal shutdown
TheMIC2179usescurrent-modecontrolwithinternalcurrent
sensing. Current-mode control provides superior line regula-
tionandmakestheregulatorcontrolloopeasytocompensate.
The output is protected with pulse-by-pulse current limiting
andthermalshutdown. Undervoltagelockoutturnstheoutput
off when the input voltage is less than 4.5V.
• Undervoltage lockout
Applications
• High-efficiency, battery-powered supplies
• Buck (step-down) dc-to-dc converters
• Cellular telephones
• Laptop computers
• Hand-held instruments
• Battery Charger
The MIC2179 and is packaged in a 20-lead SSOP package
with an operating temperature range of –40°C to +85°C.
Typical Application
VIN
5.4V to 16.5V
C1
10µF
16,17
U1
20V
R1
L1
VIN
20k
15
6
22µH
EN
3,4
VOUT
SW
PGND
FB
3.3V/600mA
Output Good
Output Low
D1
MBRM120
PWRGD
1,2,
C2
MIC
2179-3.3
19,20
100µF
6.3V
5
Skip Mode
PWM Mode
PWM
13
7
SYNC
COMP
8
SGND
9–12
BIAS
14
C3
0.01µF
R5
4.02k
Pins 4 and 18 are not connected.
C4
6.8nF
Pins 3 and 4 can be connected
together for a low-impedance
connection.
Micrel, Inc. • 2180 Fortune Drive • San Jose, CA 95131 • USA • tel + 1 (408) 944-0800 • fax + 1 (408) 474-1000 • http://www.micrel.com
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MIC2179
Ordering Information
Part Number
Voltage
Temperature Range
Package
Standard*
Pb-Free
MIC2179BSM
MIC2179YSM
Adj.
3.3V
5.0V
-40°C to +85°C
-40°C to +85°C
-40°C to +85°C
20-Lead SSOP
20-Lead SSOP
20-Lead SSOP
MIC2179-3.3BSM MIC2179-3.3YSM
MIC2179-5.0BSM MIC2179-5.0YSM
* Standard product will be supported as Pb-Free IAW PCCN #040004 effective 1-1-2005 pending residual depletion.
Pin Configuration
PGND 1
20 PGND
PGND
SW
PGND
NC
2
3
19
18
17
16
15
14
13
12
11
NC
VIN
4
VIN
5
PWM
PWRGD
FB
EN
6
BIAS
SYNC
SGND
SGND
7
COMP
SGND
SGND
8
9
10
20-Lead Wide SSOP
Pin Description
Pin Number
Pin Name
PGND
SW
Pin Function
1, 2, 19, 20
Power Ground: Connect all pins to central ground point.
Switch (Output): Internal power MOSFET output switches.
3
5
PWM
PWM/Skip-Mode Control (Input): Logic-level input. Controls regulator
operating mode. Logic low enables PWM mode. Logic high enables skip
mode. Do not allow pin to float.
6
PWRGD
Error Flag (Output): Open-drain output. Active low when FB input is 10%
below the reference voltage (VREF).
7
FB
Feedback (Input): Connect to output voltage divider resistors.
8
COMP
Compensation: Output of internal error amplifier. Connect capacitor or
series RC network to compensate the regulator control loop.
9–12
13
SGND
SYNC
Signal Ground: Connect all pins to ground, PGND.
Frequency Synchronization (Input): Optional. Connect an external clock
signal to synchronize the oscillator. Leading edge of signal above 1.7V
terminates switching cycle. Connect to SGND if not used.
14
15
BIAS
EN
Internal 3.3V Bias Supply: Decouple with 0.01µF bypass capacitor to
SGND. Do not apply any external load.
Enable (Input): Logic high enables operation. Logic low shuts down
regulator. Do not allow pin to float.
16, 17
4, 18
VIN
NC
Supply Voltage (Input): Requires bypass capacitor to PGND. Both pins
must be connected to VIN.
not internally connected.
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MIC2179
Absolute Maximum Ratings(1)
Operating Ratings(2)
Supply Voltage [100ms transient] (V ) .........................18V
Supply Voltage (V ).......................................4.5V to 16.5V
IN
IN
...................................................
Output Switch Voltage (V
)
18V
Junction Temperature Range (T ) ............ –40°C to +125°C
SW
J
Output Switch Current (I )......................................... 6.0A
SW
Enable, PWM Control Voltage (V , V
)..................18V
EN
PWM
Sync Voltage (V
)......................................................6V
SYNC
Electrical Characteristics(3)
VIN = 7.0V; TA = 25°C, bold indicates –40°C ≤ TA ≤ 85°C; unless noted.
Symbol
Parameter
Condition
Min
Typ
Max
Units
ISS
Input Supply Current
PWM mode, output not switching,
4.5V ≤ VIN ≤ 16.5V
1.0
1.5
mA
skip mode, output not switching,
600
750
µA
4.5V ≤ VIN ≤ 16.5V
VEN = 0V, 4.5V ≤ VIN ≤ 16.5V
VIN = 16.5V
1
25
3.4
µA
V
VBIAS
VFB
Bias Regulator Output Voltage
Feedback Voltage
3.10
3.30
1.245
3.3
MIC2179 [adj.]: VOUT = 3.3V, ILOAD = 0
1.22
1.27
V
VOUT
Output Voltage
MIC2179 [adj.]: VOUT = 3.3V,
5V ≤ VIN ≤ 16V, 10mA ≤ ILOAD ≤ 1A
3.20
3.14
3.40
3.46
V
V
MIC2179-5.0: ILOAD = 0
4.85
5.0
5.0
5.15
V
MIC2179-5.0:
4.85
5.15
6V ≤ VIN ≤ 16V, 10mA ≤ ILOAD ≤ 1A
4.75
5.25
V
V
MIC2179-3.3: ILOAD = 0
3.20
3.3
3.3
3.40
MIC2179-3.3:
5V ≤ VIN ≤ 16V, 10mA ≤ ILOAD ≤ 1A
3.20
3.14
3.40
3.46
V
V
VTH
VTL
IFB
Undervoltage Lockout
Feedback Bias Current
upper threshold
lower threshold
MIC2179 [adj.]
4.25
4.15
60
4.35
V
V
3.90
150
40
nA
µA
MIC2179-5.0, MIC2179-3.3
0.6V ≤ VCOMP ≤ 0.8V
upper limit
20
AVOL
Error Amplifier Gain
15
18
20
Error Amplifier Output Swing
0.9
1.5
0.05
25
V
V
lower limit
0.1
35
Error Amplifier Output Current
Oscillator Frequency
Maximum Duty Cycle
Minimum On-Time
source and sink
15
µA
kHz
%
fO
160
100
200
240
DMAX
tON min
VFB = 1.0V
VFB = 1.5V
300
1.6
400
300
2.2
ns
SYNC Frequency Range
SYNC Threshold
220
0.8
500
–1
kHz
V
SYNC Minimum Pulse Width
SYNC Leakage
ns
ISYNC
ILIM
VSYNC = 0V to 5.5V
PWM mode, VIN = 12V
skip mode
0.01
4.3
600
160
140
1
1
µA
A
Current Limit
3.4
5.5
mA
mΩ
mΩ
µA
RON
ISW
Switch On-Resistance
Output Switch Leakage
high-side switch, VIN = 12V
low-side switch, VIN = 12V
VSW = 16.5V
350
350
10
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MIC2179
Symbol
Parameter
Condition
Min
0.8
Typ
1.6
Max
2.2
1
Units
V
Enable Threshold
Enable Leakage
PWM Threshold
PWM Leakage
PWRGD Threshold
IEN
VEN = 0V to 5.5V
–1
0.01
1.1
µA
V
0.6
1.4
1
IPWM
VPWM = 0V to 5.5V
–1
0.01
1.13
4.54
3.00
0.25
0.01
µA
V
MIC2179 [adj.]: measured at FB pin
MIC2179-5.0: measured at FB pin
MIC2179-3.3: measured at FB pin
ISINK = 1.0mA
1.09
4.33
2.87
1.17
4.75
3.13
0.4
1
V
V
PWRGD Output Low
PWRGD Off Leakage
V
VPWRGD = 5.5V
µA
Notes:
1. Exceeding the absolute maximum rating may damage the device.
2. The device is not guaranteed to function outside its operating rating.
3. Specification for packaged product only.
General. Devices are ESD sensitive. Handling precautions recommended.
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MIC2179
Typical Characteristics
Oscillator Frequency
vs. Temperature
Reference Voltage
vs. Temperature
Reference Voltage
vs. Temperature
1.252
1.250
1.248
1.246
1.244
1.242
1.240
1.238
3.320
3.315
3.310
3.305
3.300
3.295
3.290
3.285
3.280
205
MIC2179 [adj.]
MIC2179-3.3
200
195
190
185
180
175
-60 -30
0
30 60 90 120 150
-60 -30
0
30 60 90 120 150
-60 -30
0
30 60 90 120 150
TEMPERATURE (°C)
TEMPERATURE (°C)
TEMPERATURE (°C)
Reference Voltage
vs. Temperature
Error-Amplifier Gain
vs. Temperature
Feedback Input Bias Current
vs. Temperature
5.030
5.020
5.010
5.000
4.990
4.980
4.970
19.0
18.5
18.0
17.5
17.0
16.5
16.0
120
MIC2179-5.0
100
80
60
40
20
0
-60 -30
0
30 60 90 120 150
-60 -30
0
30 60 90 120 150
-60 -30
0
30 60 90 120 150
TEMPERATURE (°C)
TEMPERATURE (°C)
TEMPERATURE (°C)
Current Limit
vs. Temperature
High-Side Switch
On-Resistance
Low-Side Switch
On-Resistance
350
300
250
200
150
100
50
400
350
300
250
200
150
100
50
5.5
5.3
5.1
4.9
4.7
4.5
4.3
4.1
3.9
3.7
3.5
125°C
125°C
85°C
25°C
0°C
85°C
25°C
0°C
0
2
0
4
6
8
10 12 14 16 18
2
4
6
8
10 12 14 16 18
-60 -30
0
30 60 90 120 150
INPUT VOLTAGE (V)
INPUT VOLTAGE (V)
TEMPERATURE (°C)
PWM-Mode
Supply-Current
Skip- and PWM-Mode
Efficiency
12
10
8
95
90
85
80
75
70
65
5.4V
PWM
OUTPUT
SWITCHING
8.4V
Skip
6
8.4V
PWM
4
5.4V
Skip
2
0
60
10
2
4
6
8
10 12 14 16 18
100
600
INPUT VOLTAGE (V)
OUTPUT CURRENT (mA)
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MIC2179
Block Diagram
VIN
4.5V to 16.5V
100µF
16 17
VIN
UVLO,
Thermal
Shutdown
R1
V
= 1.245
(
+ 1
)
R2
OUT
110mΩ
P-channel
ISENSE
Amp.
Output
Control
Logic
L
VOUT
SW
3
EN
15
3.3V
Regulator
Enable
Shutdown
D
COUT
BIAS
110mΩ
14
PGND
N-channel
R3
4.02k
0.01µF
1
internal
2
*
ILIMIT
Comp.
supplyVoltage
19
20
* Connect
GNDto PGND
PWM
PWM/
Skip-Mode
Select
S
Skip Mode
PWM Mode
ILIMIT
Thresh.
Voltage
5
Bold lines indicate
high current traces
Corrective
Ramp
SYNC
Stop
200kHz
Oscillator
13
R1
Skip-Mode
Comp.
Reset
Pulse
FB
7
R
S
Q
R2
VIN
Power Good
Comp.
20k
PWM
Comp.
PWRGD
6
Output Good
RC
COMP
8
CC
1.13V
VREF 1.245V
MIC2179 [Adjustable]
9
10 11 12
SGND
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MIC2179
connect an external load to the BIAS pin. It is not designed
to provide an external supply voltage.
Functional Description
Micrel’s MIC2179 is a synchronous buck regulator that oper-
ates from an input voltage of 4.5V to 16.5V and provides a
regulated output voltage of 1.25V to 16.5V. Its has internal
power MOSFETs that supply up to 1.5A load current and
operates with up to 100% duty cycle to allow low-dropout
operation. To optimize efficiency, the MIC2179 operates in
PWM and skip mode. Skip mode provides the best efficiency
when load current is less than 150mA, while PWM mode is
more efficient at higher current. PWM or skip-mode opera-
tion is selected externally, allowing an intelligent system (i.e.
microprocessor controlled) to select the correct operating
mode for efficiency and noise requirements.
Frequency Synchronization
The MIC2179 operates at a preset switching frequency of
200kHz. It can be synchronized to a higher frequency by con-
necting an external clock to the SYNC pin. The SYNC pin is
a logic level input that synchronizes the oscillator to the rising
edge of an external clock signal. It has a frequency range of
220kHz to 300kHz, and can operate with a minimum pulse
width of 500ns. If synchronization is not required, connect
SYNC to ground.
Power Good Flag
The power good flag (PWRGD) is an error flag that alerts a
system when the output is not in regulation. When the output
voltage is 10% below its nominal value, PWRGD is logic low,
During PWM operation, the MIC2179 uses current-mode
control which provides superior line regulation and makes
the control loop easier to compensate. The PWM switching
frequencyissetinternallyto200kHzandcanbesynchronized
to an external clock frequency up to 300kHz. Other features
include a low-current shutdown mode, current limit, under-
voltage lockout, and thermal shutdown. See the following
sections for more detail.
signalingthatV
istolow. PWRGDisanopen-drainoutput
OUT
that can sink 1mA from a pull-up resistor connected to V .
IN
Low-Dropout Operation
Output regulation is maintained in PWM or skip mode even
when the difference between V and V
decreases below
IN
OUT
1V. As V – V
decreases, the duty cycle increases until
IN
OUT
Switch Output
it reaches 100%. At this point, the P-channel is kept on for
several cycles at a time, and the output stays in regulation
The switch output (SW) is a half H-bridge consisting of a
high-sideP-channelandlow-sideN-channelpowerMOSFET.
TheseMOSFETshaveatypicalon-resistanceof150mΩwhen
the MIC2179 operates from a 12V supply. Antishoot-through
circuitry prevents the P-channel and N-channel from turning
on at the same time.
until V – V
falls below the dropout voltage (dropout
IN
OUT
voltage = P-channel on-resistance × load current).
PWM-Mode Operation
Refer to “PWM Mode Functional Diagram” which is a simpli-
fied block diagram of the MIC2179 operating in PWM mode
and its associated waveforms.
Current Limit
The MIC2179 uses pulse-by-pulse current limiting to protect
the output. During each switching period, a current limit com-
paratordetectsiftheP-Channelcurrentexceeds4.3A. When
it does, the P-channel is turned off until the next switching
period begins.
When operating in PWM mode, the output P-channel and N-
channel MOSFETs are alternately switched on at a constant
frequency and variable duty cycle. Aswitching period begins
whentheoscillator generates aresetpulse.Thispulse resets
the RS latch which turns on the P-channel and turns off the
Undervoltage Lockout
N-channel. During this time, inductor current (I ) increases
L1
Undervoltage lockout (UVLO) turns off the output when the
and energy is stored in the inductor. The current sense ampli-
input voltage (V ) is to low to provide sufficient gate drive
for the output MOSFETs. It prevents the output from turning
fier (I
Amp) measures the P-channel drain-to-source
IN
SENSE
voltage and outputs a voltage proportional to I . The output
L1
on until V exceeds 4.3V. Once operating, the output will
of I
Amp is added to a sawtooth waveform (corrective
IN
SENSE
not shut off until V drops below 4.2V.
ramp)generatedbytheoscillator,creatingacompositewave-
form labeled I on the timing diagram. When I is
IN
Thermal Shutdown
SENSE
SENSE
greater than the error amplifier output, the PWM comparator
will set the RS latch which turns off the P-channel and turns
on the N-channel. Energy is then discharged from the induc-
Thermal shutdown turns off the output when the MIC2179
junction temperature exceeds the maximum value for safe
operation. After thermal shutdown occurs, the output will not
turn on until the junction temperature drops approximately
10°C.
tor and I decreases until the next switching cycle begins.
L1
By varying the P-channel on-time (duty cycle), the average
inductor current is adjusted to whatever value is required to
regulate the output voltage.
Shutdown Mode
The MIC2179 has a low-current shutdown mode that is con-
trolled by the enable input (EN). When a logic 0 is applied
to EN, the MIC2179 is in shutdown mode, and its quiescent
current drops to less than 5µA.
The MIC2179 uses current-mode control to adjust the duty
cycle and regulate the output voltage. Current-mode control
has two signal loops that determine the duty cycle. One is an
outer loop that senses the output voltage, and the other is
a faster inner loop that senses the inductor current. Signals
from these two loops control the duty cycle in the following
Internal Bias Regulator
An internal 3.3V regulator provides power to the MIC2179
control circuits.Thisinternal supply isbrought outtotheBIAS
pin for bypassing by an external 0.01µF capacitor. Do not
way: V
is fed back to the error amplifier which compares
OUT
the feedback voltage (V ) to an internal reference voltage
FB
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(V ). When V
MIC2179
is lower than its nominal value, the error
the P-channel. The output switch voltage (V ) then swings
REF
OUT
SW
amplifieroutputvoltageincreases.Thisvoltagethenintersects
the current sense waveform later in switching period which
increases the duty cycle and the average inductor current. If
from V to 0.4V below ground, and I flows through the
IN
L1
Schottky diode. L1 discharges its energy to the output and
decreases to zero. When I = 0, V swings from –0.4V
I
L1
L1
SW
V
ishigherthannominal,theerroramplifieroutputvoltage
to V
, and this triggers a one-shot that resets the RS latch.
OUT
OUT
decreases, reducing the duty cycle.
ResettingtheRSlatchturnsontheP-channel,andthisbegins
another switching cycle.
The PWM control loop is stabilized in two ways. First, the
innersignalloopiscompensatedbyaddingacorrectiveramp
to the output of the current sense amplifier. This allows the
regulator to remain stable when operating at greater than
50% duty cycle. Second, a series resistor-capacitor load
is connected to the error amplifier output (COMP pin). This
places a pole-zero pair in the regulator control loop.
The skip-mode comparator regulates V
by controlling
OUT
when the MIC2179 skips cycles. It compares V to V
FB
REF
and has 10mV of hysteresis to prevent oscillations in the
control loop. When V is less than V – 5mV, the com-
FB
REF
parator output is logic 1, allowing the P-channel to turn on.
Conversely, when V is greater than V
+ 5mV, the P-
FB
REF
channel is turned off.
One more important item is synchronous rectification. As
mentioned earlier, the N-channel output MOSFET is turned
on after the P-channel turns off. When the N-channel turns
on, its on-resistance is low enough to create a short across
the output diode. As a result, inductor current flows through
the N-channel and the voltage drop across it is significantly
lower than a diode forward voltage. This reduces power dis-
sipation and improves efficiency to greater than 95% under
certain operating conditions.
Note that this is a self oscillating topology which explains
why the switching frequency and duty cycle are a function
of V , V
, and the value of L1. It has the unique feature
IN
OUT
(for a pulse-skipping regulator) of supplying the same value
of maximum load current for any value of V , V , or L1.
This allows the MIC2179 to always supply up to 300mA of
load current when operating in skip mode.
IN
OUT
Selecting PWM- or Skip-Mode Operation
To prevent shoot through current, the output stage employs
break-before-makecircuitrythatprovidesapproximately50ns
of delay from the time one MOSFET turns off and the other
turns on. As a result, inductor current briefly flows through
the output diode during this transition.
PWM or skip mode operation is selected by an external
logic signal applied to the PWM pin. A logic low places the
MIC2179 into PWM mode, and logic high places it into skip
mode.Skipmodeoperationprovidesthebestefficiencywhen
load current is less than 150mA, and PWM operation is more
efficient at higher currents.
Skip-Mode Operation
Referto“SkipModeFunctionalDiagram”whichisasimplified
block diagram of the MIC2179 operating in skip mode and
its associated waveforms.
The MIC2179 was designed to be used in intelligent sys-
tems that determine when it should operate in PWM or skip
mode. This makes the MIC2179 ideal for applications where
a regulator must guarantee low noise operation when sup-
plying light load currents, such as cellular telephone, audio,
and multimedia circuits.
Skip-mode operation turns on the output P-channel at a
frequency and duty cycle that is a function of V , V
, and
IN OUT
the output inductor value. While in skip mode, the N-chan-
nel is kept off to optimize efficiency by reducing gate charge
There are two important items to be aware of when selecting
PWM or skip mode. First, the MIC2179 can start-up only in
PWM mode, and therefore requires a logic low at PWM dur-
ing start-up. Second, in skip mode, the MIC2179 will supply
a maximum load current of approximately 300mA, so the
output will drop out of regulation when load current exceeds
this limit. To prevent this from occurring, the MIC2179 should
change from skip to PWM mode when load current exceeds
200mA.
dissipation. V
is regulated by skipping switching cycles
OUT
that turn on the P-channel.
To begin analyzing MIC2179 skip mode operation, assume
the skip-mode comparator output is high and the latch out-
put has been reset to a logic 1. This turns on the P-channel
and causes I to increase linearly until it reaches a current
L1
limit of 400mA. When I reaches this value, the current limit
L1
comparator sets the RS latch output to logic 0, turning off
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MIC2179
PWM-Mode Functional Diagram
VIN
4.5V to 16.5V
CIN
VIN
16 17
R1
R2
VOUT = 1.245
(
+ 1)
110mΩ
P-channel
ISENSE
Amp.
L1
IL1
COUT
VOUT
SW
3
D
110mΩ
PGND
1
N-channel
2
19
20
Corrective
Ramp
SYNC
Stop
200kHz
13
Oscillator
R1
Reset
Pulse
FB
7
R2
R
Q
PWM
S
Comp.
Error
Amp.
COMP
8
RC
CC
VREF1.245V
MIC2179 [Adjustable] PWM-Mode Signal Path
SGND
9
10 11 12
VSW
Reset
Pulse
ILOAD
IL1
∆IL1
Error Amp.
Output
ISENSE
June 2009
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M9999-063009
Micrel, Inc.
MIC2179
Skip-Mode Functional Diagram
VIN
4.5V to 16.5V
CIN
VIN
16 17
Output Control Logic
S
R
Q
R1
R2
VOUT = 1.245
(
+ 1)
110mΩ
P-channel
One
Shot
ISENSE
Amp.
L1
IL1
COUT
VOUT
SW
3
D
PGND
1
2
ILIMIT
Comp.
19
20
ILIMIT
Thresh.
Voltage
R1
R2
Skip-Mode
Comp.
FB
7
VREF1.245V
MIC2179 [Adjustable] Skip-Mode Signal Path
9
10 11 12
SGND
VIN
VOUT
VSW
0
One-Shot
Pulse
ILIM
IL1
0
VREF+ 5mV
VFB
VREF– 5mV
June 2009
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M9999-063009
Micrel, Inc.
MIC2179
To maximize efficiency, the inductor’s resistance must
be less than the output switch on-resistance (preferably,
50mΩ or less).
Application Information
Feedback Resistor Selection (Adjustable Version)
The output voltage is programmed by connecting an external
resistive divider to the FB pin as shown in “MIC2179 Block
Diagram.” TheratioofR1toR2determinestheoutputvoltage.
Tooptimizeefficiencyduringlowoutputcurrentoperation, R2
should not be less than 20kΩ. However, to prevent feedback
error due to input bias current at the FB pin, R2 should not
be greater than 100kΩ. After selecting R2, calculate R1 with
the following formula:
Output Capacitor Selection
Select an output capacitor that has a low value of ESR.
This parameter determines a regulator’s output ripple volt-
age (V
) which is generated by ∆I × ESR. Therefore,
RIPPLE
L
ESR must be equal or less than a maximum value calculated
for a specified V
(typically less than 1% of the output
RIPPLE
voltage) and ∆I
:
L(max)
VRIPPLE
VOUT
ESR MAX
=
R1 = R2 ((1.245V ) -1)
∆IL(max)
Typically, capacitors in the range of 100 to 220µF have ESR
less than this maximum value. The output capacitor can be
a low ESR electrolytic or tantalum capacitor, but tantalum is
a better choice for compact layout and operation at tempera-
tures below 0°C. The voltage rating of a tantalum capacitor
Input Capacitor Selection
TheinputcapacitorisselectedforitsRMScurrentandvoltage
ratingandshouldbealowESR(equivalentseriesresistance)
electrolytic or tantalum capacitor. As a rule of thumb, the
voltage rating for a tantalum capacitor should be twice the
must be 2 × V
must be 1.4 × V
, and the voltage rating of an electrolytic
.
OUT
value of V , and the voltage rating for an electrolytic should
IN
OUT
be 40% higher than V
The RMS current rating must be
IN.
Output Diode Selection
equal or greater than the maximum RMS input ripple cur-
rent. A simple, worst case formula for calculating this RMS
current is:
In PWM operation, inductor current flows through the output
diode approximately 50ns during the dead time when one
output MOSFET turns off the other turns on. In skip mode,
the inductor current flows through the diode during the entire
P-channel off time. The correct diode for both of these condi-
tions is a 1A diode with a reverse voltage rating greater than
ILOAD(max)
IRMS(max)
=
2
Tantalum capacitors are a better choice for applications that
require the most compact layout or operation below 0°C.
The input capacitor must be located very close to the VIN
pin (within 0.2in, 5mm). Also, place a 0.1µF ceramic bypass
capacitor as close as possible to VIN.
V . It must be a schottky or ultrafast-recovery diode
IN
(t < 100ns) to minimize power dissipation from the diode’s
R
reverse-recovery charge.
Compensation
Inductor Selection
Compensation is provided by connecting a series RC load
to the COMP pin. This creates a pole-zero pair in the regu-
lator control loop, allowing the regulator to remain stable
with enough low frequency loop-gain for good load and line
regulation. At higher frequencies, the pole-zero reduces
loop-gain to a level referred to as the mid-band gain. The
mid-band gain is low enough so that the loop gain crosses
0db with sufficient phase margin. Typical values for the RC
load are 4.7nF to 10nF for the capacitor and 5kΩ to 20kΩ
for the resistor.
The MIC2179 is a current-mode controller with internal slope
compensation. As a result, the inductor must be at least a
minimum value to prevent subharmonic oscillations. This
minimum value is calculated by the following formula:
LMIN = VOUT x 3.0 µH/V
In general, a value at least 20% greater than L
should
MIN
be selected because inductor values have a tolerance of
±20%.
Two other parameters to consider in selecting an inductor
are winding resistance and peak current rating. The inductor
must have a peak current rating equal or greater than the
peak inductor current. Otherwise, the inductor may satu-
rate, causing excessive current in the output switch. Also,
the inductor’s core loss may increase significantly. Both of
these effects will degrade efficiency. The formula for peak
inductor current is:
Printed Circuit Board Layout
A well designed PC board will prevent switching noise and
ground bounce from interfering with the operation of the
MIC2179. Agooddesigntakesintoconsiderationcomponent
placement and routing of power traces.
The first thing to consider is the locations of the input ca-
pacitor, inductor, output diode, and output capacitor. The
input capacitor must be placed very close to the VIN pin,
the inductor and output diode very close to the SW pin, and
the output capacitor near the inductor. These components
pass large high-frequency current pulses, so they must use
short, wide power traces. In addition, their ground pins and
PGND are connected to a ground plane that is nearest the
power supply ground bus.
∆IL(max)
IL(peak) = ILOAD(max)
Where:
∆IL(max) = VOUT (1 -
+
2
VOUT
1
) x
VIN(max)
L • f
June 2009
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M9999-063009
Micrel, Inc.
MIC2179
The feedback resistors, RC compensation network, and
BIAS pin bypass capacitor should be located close to their
respective pins. To prevent ground bounce, their ground
traces and SGND should not be in the path of switching
currents returning to the power supply ground bus. SGND
and PGND should be tied together by a ground plane that
extends under the MIC2179.
Suggested Manufacturers List
Inductors
Capacitors
Diodes
Transistors
Coilcraft
1102 Silver Lake Rd.
Cary, IL 60013
tel: (708) 639-2361
fax: (708) 639-1469
AVX Corp.
General Instruments (GI)
10 Melville Park Rd.
Melville, NY 11747
tel: (516) 847-3222
fax: (516) 847-3150
Siliconix
801 17th Ave. South
Myrtle Beach, SC 29577
tel: (803) 448-9411
fax: (803) 448-1943
2201 Laurelwood Rd.
Santa Clara, CA 96056
tel: (800) 554-5565
Coiltronics
Sanyo Video Components Corp.
2001 Sanyo Ave.
San Diego, CA 92173
tel: (619) 661-6835
International Rectifier Corp.
233 Kansas St.
El Segundo, CA 90245
tel: (310) 322-3331
fax: (310) 322-3332
6000 Park of Commerce Blvd.
Boca Raton, FL 33487
tel: (407) 241-7876
fax: (407) 241-9339
fax: (619) 661-1055
Bi Technologies
4200 Bonita Place
Fullerton, CA
tel: (714) 447-2345
fax: (714) 447-2500
Sprague Electric
Lower Main St.
60005 Sanford, ME 04073
tel: (207) 324-4140
Motorola Inc.
MS 56-126
3102 North 56th St.
Phoenix, AZ 85018
tel: (602) 244-3576
fax: (602) 244-4015
June 2009
12
M9999-063009
Micrel, Inc.
MIC2179
Package Information
20-Pin SSOP (SM)
MICREL INC. 2180 FORTUNE DRIVE SAN JOSE, CA 95131 USA
tel + 1 (408) 944-0800 fax + 1 (408) 474-1000 web http://www.micrel.com
This information furnished by Micrel in this data sheet is believed to be accurate and reliable. However no responsibility is assumed by Micrel for its use.
Micrel reserves the right to change circuitry and specifications at any time without notification to the customer.
Micrel Products are not designed or authorized for use as components in life support appliances, devices or systems where malfunction of a product can
reasonably be expected to result in personal injury. Life support devices or systems are devices or systems that (a) are intended for surgical implant into
the body or (b) support or sustain life, and whose failure to perform can be reasonably expected to result in a significant injury to the user. A Purchaser's
use or sale of Micrel Products for use in life support appliances, devices or systems is a Purchaser's own risk and Purchaser agrees to fully indemnify
Micrel for any damages resulting from such use or sale.
© 2001 Micrel Incorporated
June 2009
13
M9999-063009
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