MP3115DT [MPS]
High-Efficiency, Single-Cell Alkaline, 1.3MHz Synchronous Step-up Converter with Output Disconnect;
| 型号： | MP3115DT |
| 厂家： | 
MONOLITHIC POWER SYSTEMS |
| 描述： | High-Efficiency, Single-Cell Alkaline, 1.3MHz Synchronous Step-up Converter with Output Disconnect |
| 文件： | 总8页 (文件大小：622K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
MP3115
High-Efficiency, Single-Cell Alkaline, 1.3MHz
Synchronous Step-up Converter
with Output Disconnect
The Future of Analog IC Technology
DESCRIPTION
FEATURES
The MP3115 is a synchronous, fixed frequency,
current mode step-up converter with output-to-
input disconnect optimized to boost a single AA
Alkaline battery to 2.5V or 3.3V.
•
•
Over 90% Efficiency
Output-to-Input Disconnect in Shutdown
Mode
Internal Synchronous Rectifier
Output Voltage up to 4.0V without an
External Schottky Diode
Inrush Current Limiting and Internal
Soft-Start
•
•
It can startup from an input voltage as low as
0.950V and provide in-rush current limiting as
well as output short circuit protection. The
integrated P-Channel synchronous rectified
switch provides improved efficiency and
eliminates an external schottky diode. The
output disconnect feature allows the output to be
completely discharged, thus allowing the part to
draw less than 1µA of current in shutdown mode.
•
•
•
•
•
•
•
Internal Compensation
1A Minimum Peak Current Limit
1.3MHz Fixed Switching Frequency
Zero Current Shutdown Mode
Thermal Shutdown
6-Pin SOT-23 Package
The 1.3MHz switching frequency allows for the
use of smaller external components and the
internal compensation and soft-start minimize
the external component count, all helping to
produce a compact solution for a wide range of
load current.
APPLICATIONS
•
•
•
•
•
Single-cell Alkaline Consumer Products
MP3 Players
Wireless Mouse
RFTags
Audio Recorders
The MP3115 regulates the output voltage up to
4.0V or 3.3V at 200mA from a single cell AA
battery, without the use of an external Schottky
diode.
“MPS” and “The Future of Analog IC Technology” are Registered Trademarks of
Monolithic Power Systems, Inc.
The MP3115 is offered in a SOT23-6 package.
EVALUATION BOARD REFERENCE
Board Number
Dimensions
EV3115DT-00A L x W x H (5cm x 5cm x 1.2cm)
TYPICAL APPLICATION
0.95V to 2.5V
1
VIN
3.3V
5
OUT
SW
VOUT
MP3115
6
4
IN
3
EN
FB
GND
EN
2
MP3115 Rev. 0.9
4/12/2016
www.MonolithicPower.com
MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited.
© 2016 MPS. All Rights Reserved.
1
MP3115 – HIGH-EFFICIENCY 1.3MHz SYNCHRONOUS STEP-UP CONVERTER
PACKAGE REFERENCE
ABSOLUTE MAXIMUM RATINGS (1)
Supply Voltage VIN...................................... 2.5V
VSW................................................ –0.3V to 6.5V
All Other Pins................................ –0.3V to 6.5V
Storage Temperature ..............–65°C to +150°C
TOP VIEW
SW
GND
FB
1
2
3
6
5
4
IN
Thermal Resistance (3)
θJA
θJC
OUT
EN
SOT23-6................................195.... 110.. °C/W
Notes:
1) Exceeding these ratings may damage the device.
2) The device is not guaranteed to function outside of its
operating conditions.
Part Number*
MP3115DT
Package
Temperature
3) Measured on approximately 1” square of 1 oz copper.
SOT23-6
–40°C to +85°C
For Tape & Reel, add suffix –Z (eg. MP3115DT–Z)
For RoHS Compliant Packaging, add suffix –LF
(eg. MP3115DT–LF–Z)
*
ELECTRICAL CHARACTERISTICS
VIN = 1.5V, VEN = VOUT = 3.3V, TA = +25°C, unless otherwise noted.
Parameter
Symbol Condition
Min
Typ
Max
1.1
0.5
4.0
1
Units
V
Minimum Startup Voltage
Minimum Operating Voltage (4)
Output Voltage Range
Supply Current (Shutdown)
Supply Current (Quiescent)
Feedback Voltage
VST
VIN
RL = 3kΩ, Rising Edge
0.95
VEN = VIN
V
VOUT
2.5
V
VEN = VOUT = 0V
VFB = 1.3V
0
200
1.225
10
μA
μA
V
VFB
fSW
Feedback Input Current
Switching Frequency
Maximum Duty Cycle
EN Input Low Voltage
EN Input High Voltage
EN Input Current
VFB = 1.2V
VFB= 1.1V
nA
MHz
%
1.3
DMAX VFB= 1.1V
85
90
0.4
1
V
0.9
V
VEN = 3V
VSW = 5.5V
0
μA
mΩ
μA
A
NMOS On Resistance
NMOS Leakage Current
NMOS Current Limit
PMOS On Resistance
PMOS Leakage Current
Thermal Shutdown (5)
Thermal Shutdown Hysteresis (5)
Minimum On Time (5)
Notes:
RNMOS
ILIM
300
1
1
1.3
600
1
RPMOS
mΩ
μA
°C
°C
ns
VEN = VOUT = 0V, VSW = 3V
160
30
100
150
4) The MP3115 is not dependent on VIN when VOUT is greater than 2.4V.
5) Guaranteed by design, not tested.
MP3115 Rev. 0.9
4/12/2016
www.MonolithicPower.com
MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited.
© 2016 MPS. All Rights Reserved.
2
MP3115 – HIGH-EFFICIENCY 1.3MHz SYNCHRONOUS STEP-UP CONVERTER
PIN FUNCTIONS
Pin # Name Description
1
SW Output Switch Node. SW is the drain of the internal N-Channel and P-Channel MOSFETs.
Connect the inductor to SW to complete the step-up converter.
2
3
GND Ground.
FB
Regulation Feedback Input. Connect an external resistive voltage divider from the output to FB
to set the output voltage.
4
5
6
EN
Regulator On/Off Control Input. A logic high input (VEN > 0.9V) turns on the regulator. A logic
low input (VEN < 0.4V) puts the MP3115 into low current shutdown mode.
OUT Supply Input for the MP3115 and Output Voltage Sense Input. Connect to the output of the
converter.
IN
Input Voltage.
MP3115 Rev. 0.9
4/12/2016
www.MonolithicPower.com
MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited.
© 2016 MPS. All Rights Reserved.
3
MP3115 – HIGH-EFFICIENCY 1.3MHz SYNCHRONOUS STEP-UP CONVERTER
TYPICAL PERFORMANCE CHARACTERISTICS
C1 = 10µF, C2=22µF, L=1.7µH,R2=20K, TA = +25ºC, unless otherwise noted.
Efficiency vs.
Load Current
Efficiency vs.
Load Current
Load Regulation
95
90
95
90
2.60
2.56
2.52
85
80
85
80
75
70
75
70
2.48
V
V
V
IN=1.5V
IN=2.5V
OUT=3.3V
V
V
IN=1.5V
OUT=2.5V
2.44
2.40
65
V
IN=1.5V
65
60
60
10
100
LOAD CURRENT (mA)
1000
10
100
LOAD CURRENT (mA)
1000
0
50
100
150
200
250
LOAD CURRENT (mA)
Minimum Start
Line Regulation
IPEAK vs. Duty Cycle
V
IN vs. IOUT
2.60
2.56
2.52
2.0
1.8
1.6
1700
1500
V
OUT=3.3V
1300
1100
1.4
1.2
2.48
2.44
2.40
900
700
V
OUT=2.5V
1.0
0.8
I
OUT=100mA
30
40
50
60
70
80
10
13
16
19
22 25
0
30
60
90
120
150
INPUT VOLTAGE (V)
OUTPUT CURRENT (mA)
Duty Cycle (%)
Inrush Current
Line Transient
Load Transient
V
EN=2V,VIN=1.5V,VOUT=3.3V
V
IN=1.2V to 2V,VOUT=2.5V, IOUT=48mA
EN=VIN,Resistor Load
V
IN=1.2V,VOUT=2.5V,IOUT=0mA to 50mA
EN=VIN,Resistor Load
IOUT=41mA,CFF=10nF
V
V
V
EN
V
OUT
2V/div.
50mV/div.
VIN
1V/div.
VOUT
2V/div.
VOUT
0.1V/div.
I
IN
I
OUT
0.2A/div.
50mA/div.
1ms/div.
200 s/div.
40 s/div.
MP3115 Rev. 0.9
4/12/2016
www.MonolithicPower.com
MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited.
© 2016 MPS. All Rights Reserved.
4
MP3115 – HIGH-EFFICIENCY 1.3MHz SYNCHRONOUS STEP-UP CONVERTER
TYPICAL PERFORMANCE CHARACTERISTICS (continued)
C1 = 10µF, C2=22µF, L=1.7µH,R2=20K, TA = +25ºC, unless otherwise noted.
VIN
1V/div.
VIN
0.5V/div.
VIN
0.5V/div.
VSW
2V/div.
VSW
2V/div.
VSW
2V/div.
VOUT
VOUT
VOUT
2V/div
2V/div
2V/div
IL
VEN
2V/div.
VEN
2V/div.
1A/div.
1ms/div
10ms/div
20ms/div.
Short Circuit
VIN=VEN=2V, VOUT=3.3V
Short Circuit Recovery
VIN=VEN=2V, VOUT=3.3V
VIN
VIN
2V/div.
2V/div.
VIN
1V/div.
VSW
2V/div.
VSW
2V/div.
VSW
2V/div.
VO
VOUT
5V/div
5V/div.
VOUT
2V/div
IL
IL
IL
0.2A/div.
0.2A/div.
1A/div.
20ms/div.
No Load Ripple
VIN=VEN=0.92V, VOUT=3.3V
IOUT=0mA
Full Load Ripple
VIN=VEN=0.95V, VOUT=3.3V
IOUT=150mA
VIN
1V/div.
VIN
1V/div.
VSW
2V/div.
VSW
2V/div.
VOUT
10mV/div
VOUT
50mV/div
IL
IL
1A/div.
1A/div.
MP3115 Rev. 0.9
4/12/2016
www.MonolithicPower.com
MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited.
© 2016 MPS. All Rights Reserved.
5
MP3115 – HIGH-EFFICIENCY 1.3MHz SYNCHRONOUS STEP-UP CONVERTER
OPERATION
6
IN
5
OUT
STARTUP
SOFT-START
PROTECTION
4
EN
OSC
1.3MHz
CONTROL
LOGIC
1
2
SW
BIAS
RAMP
+
RSENSE
CURRENT
SENSE
AMPLIFIER
GND
PWM
COMPARATOR
3
FB
ERROR
AMPLIFIER
Figure 1—Functional Block Diagram
The MP3115 uses a 1.3MHz fixed-frequency,
current-mode regulation architecture to regulate
the output voltage. The MP3115 measures the
output voltage through an external resistive
voltage divider and compares that to the
internal 1.2V reference to generate the error
voltage. The current-mode regulator compares
the error voltage to the inductor current to
regulate the output voltage. The use of current-
mode regulation improves transient response
and control loop stability.
At the beginning of each cycle, the N-channel
MOSFET switch is turned on, forcing the
inductor current to rise. The current at the
source of the switch is internally measured and
converted to a voltage by the current sense
amplifier. That voltage is compared to the error
voltage. When the inductor current rises
sufficiently, the PWM comparator turns off the
switch, forcing the inductor current to the output
capacitor through the internal P-Channel
MOSFET rectifier, which forces the inductor
current to decrease. The peak inductor current
is controlled by the error voltage, which in turn
is controlled by the output voltage. Thus the
output voltage controls the inductor current to
satisfy the load.
When the MP3115 is disabled (EN<0.4V), both
power switches are off. The body of the
P-Channel MOSFET connects to SW thus there
is no current path from SW to OUT. When the
MP3115 is enabled (EN>0.8V), the P-Channel
MOSFET turns on to charge the output
capacitor to a voltage close to the input voltage.
During this time, the gate of the P-Channel is
controlled to limit the chip power dissipation.
The MP3115 starts switching when the output
voltage is close to the input voltage. If the input
voltage is less than 1.6V, the MP3115 will start
with CCM (constant current mode) until the
output voltage crosses 1.6V. After that, the
soft-start circuit will take over to bring the output
voltage to the regulated value.
The MP3115 has a temperature sensing circuit
to protect the part. The MP3115 turns off both
switches when the chip temperature reaches
150°C.
MP3115 Rev. 0.9
4/12/2016
www.MonolithicPower.com
MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited.
© 2016 MPS. All Rights Reserved.
6
MP3115 – HIGH-EFFICIENCY 1.3MHz SYNCHRONOUS STEP-UP CONVERTER
APPLICATION INFORMATION
Selecting the Inductor
COMPONENT SELECTION
The inductor is required to force the output
voltage higher while being driven by the lower
input voltage. A good rule for determining the
inductance is to allow the peak-to-peak ripple
current to be approximately 30%-50% of the
maximum input current. Make sure that the
peak inductor current is below the minimum
current limit at the duty cycle used to prevent
loss of regulation due to current limit variation.
Setting the Output Voltage
Set the output voltage by selecting the resistive
voltage divider ratio. The voltage divider drops
the output voltage to the 1.2V feedback voltage.
Use 20kΩ for the low-side resistor (R2) of the
voltage divider. Determine the high-side resistor
(R1) by the equation:
VOUT − VFB
R1=
V
⎛
⎞
FB
Calculate the required inductance value L using
the equations:
⎜
⎜
⎟
⎟
R2
⎝
⎠
Where VOUT is the output voltage, VFB is the
1.2V feedback voltage and R2=20kΩ.
VIN(VOUT - VIN )
L =
VOUT × fSW × ΔI
Selecting the Input Capacitor
VOUT ×ILOAD
(MAX)
An input capacitor is required to supply the AC
ripple current to the inductor while limiting noise
at the input source. Multi-layer ceramic
capacitors are recommended as they have
extremely low ESR and are available in small
footprints. Use an input capacitor of 4.7μF or
greater, and place it physically close to the
device.
IIN(MAX)
=
VIN ×η
30% − 50% IIN(MAX)
ΔI =
)
Where ILOAD(MAX) is the maximum load current, ΔI
is the peak-to-peak inductor ripple current and η
is the efficiency. For the MP3115, 4.7µH is
recommended for most applications. Choose an
inductor that does not saturate at the peak
switch current as calculated above with
additional margin to cover for heavy load
transients and extreme startup conditions.
Selecting the Output Capacitor
A single 4.7µF to 10µF ceramic capacitor
normally provides sufficient output capacitance
for most applications. Larger values (up to 22µF)
may be used to obtain extremely low output
voltage ripple and improve transient response.
The impedance of the ceramic capacitor at the
switching frequency is dominated by its
capacitance, so the output voltage ripple is
mostly independent of ESR. The output voltage
ripple VRIPPLE is calculated as:
Selecting the Feed-Forward Capacitor
A feed-forward capacitor in parallel with the
high-side resistor R1 can be added to improve
the output ripple at both discontinuous
conduction modes and the load transient
response. A 47pF capacitor is recommended
for most applications.
ILOAD
UT
VO − VIN
UT
LAYOUT CONSIDERATIONS
VRIPPLE
=
VO × C2× fSW
High frequency switching regulators require
very careful layout for stable operation and low
noise. All components must be placed as close
to the IC as possible. All feedback components
must be kept close to the FB pin to prevent
noise injection on the FB pin trace. The ground
return of C1 and C2 should be tied close to the
GND pin. See the MP3115 demo board layout
for reference.
Where VIN is the input voltage, ILOAD is the load
current, C2 is the capacitance of the output
capacitor and fSW is the 1.3MHz switching
frequency.
MP3115 Rev. 0.9
4/12/2016
www.MonolithicPower.com
MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited.
© 2016 MPS. All Rights Reserved.
7
MP3115 – HIGH-EFFICIENCY 1.3MHz SYNCHRONOUS STEP-UP CONVERTER
PACKAGE INFORMATION
SOT23-6
PACKAGE OUTLINE DRAWING FOR 6-SOT23
MF-PO-D-0032 revision 2.1
0.95
BSC
0.60
TYP
2.80
3.00
6
4
1.20
TYP
See Note 7
EXAMPLE
TOP MARK
1.50
1.70
2.60
TYP
2.60
3.00
AAAA
PIN 1
1
3
TOP VIEW
RECOMMENDED LAND PATTERN
0.90
1.30
1.45 MAX
0.09
0.20
SEATING PLANE
0.30
0.50
0.00
0.15
SEE DETAIL "A"
0.95 BSC
FRONT VIEW
SIDE VIEW
NOTE:
1) ALL DIMENSIONS ARE IN MILLIMETERS.
2) PACKAGE LENGTH DOES NOT INCLUDE MOLD FLASH,
PROTRUSION OR GATE BURR.
GAUGE PLANE
0.25 BSC
3) PACKAGE WIDTH DOES NOT INCLUDE INTERLEAD FLASH
OR PROTRUSION.
4) LEAD COPLANARITY (BOTTOM OF LEADS AFTER FORMING)
SHALL BE 0.10 MILLIMETERS MAX.
5) DRAWING CONFORMS TO JEDEC MO-178, VARIATION AB.
6) DRAWING IS NOT TO SCALE.
0.30
0.55
0o-8o
7) PIN 1 IS LOWER LEFT PIN WHEN READING TOP MARK FROM
LEFT TO RIGHT, (SEE EXAMPLE TOP MARK)
NOTICE: The information in this document is subject to change without notice. Users should warrant and guarantee that third
party Intellectual Property rights are not infringed upon when integrating MPS products into any application. MPS will not
assume any legal responsibility for any said applications.
MP3115 Rev. 0.9
4/12/2016
www.MonolithicPower.com
MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited.
© 2016 MPS. All Rights Reserved.
8
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