SS34 [MPS]
2A, 32V, 330KHz Step-Down Converter; 2A ， 32V ，为330kHz降压转换器
| 型号： | SS34 |
| 厂家： | 
MONOLITHIC POWER SYSTEMS |
| 描述： | 2A, 32V, 330KHz Step-Down Converter |
| 文件： | 总10页 (文件大小：225K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
TM
MP1591
2A, 32V, 330KHz
Step-Down Converter
TM
The Future of Analog IC Technology
DESCRIPTION
FEATURES
The MP1591 is a high voltage step-down
converter ideal for automotive power adapter
battery chargers. Its wide 6.5V to 32V input
voltage range covers the automotive battery’s
requirements and it achieves 2A continuous
output for quick charge capability.
•
•
•
•
•
Wide 6.5V to 32V Input Operating Range
34V Absolute Maximum Input
2A Output Current
120mΩ Internal Power MOSFET Switch
Stable with Low ESR Output Ceramic
Capacitors
•
•
•
•
•
•
•
•
•
Up to 95% Efficiency
20µA Shutdown Mode
Fixed 330KHz Frequency
Thermal Shutdown
Cycle-by-Cycle Over Current Protection
Output Adjustable From 1.23V to 21V
Under Voltage Lockout
Reference Voltage Output
Available in 8-Pin SOIC Packages
Current mode operation provides fast transient
response and eases loop stabilization. Fault
protection includes cycle-by-cycle current
limiting and thermal shutdown. In shutdown
mode, the converter draws only 20µA of supply
current.
The MP1591 requires a minimum number of
readily available external components to
complete a 2A step-down DC to DC converter
solution.
APPLICATIONS
EVALUATION BOARD REFERENCE
•
•
•
•
Automotive Power Adapters
PDA and Cellular Phone Battery Chargers
Distributed Power Systems
Board Number
Dimensions
EV0020
2.1”X x 1.4”Y x 0.5”Z
Automotive Aftermarket Electronics
“MPS” and “The Future of Analog IC Technology” are Trademarks of Monolithic
Power Systems, Inc.
TYPICAL APPLICATION
C2
10nF
Efficiency vs
INPUT
6.5V to 32V
Load Current
100
V
=5V
OUT
90
80
70
60
50
40
30
20
2
1
V
=3.3V
OUT
IN
BS
OUTPUT
2.5V
2A
7
8
3
EN
SW
OFF ON
MP1591
D1
5
OPEN
NOT USED
REF
GND
FB
COMP
4
6
C4
4.7nF
C3
V
=12V
IN
OPEN
0
0.5
1
1.5
2
LOAD CURRENT (A)
MP1591_EC01
MP1591_TAC_S01
MP1591 Rev. 2.1
12/5/2005
www.MonolithicPower.com
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© 2005 MPS. All Rights Reserved.
1
TM
MP1591 – 2A, 32V, 330KHz STEP-DOWN CONVERTER
PACKAGE REFERENCE
ABSOLUTE MAXIMUM RATINGS (1)
IN Supply Voltage........................–0.3V to +34V
SW Voltage............................. –1V to VIN + 0.3V
BS Voltage ....................VSW – 0.3V to VSW + 6V
All Other Pins.................................–0.3V to +6V
Junction Temperature...............................150°C
Lead Temperature....................................260°C
Storage Temperature ..............–65°C to +150°C
Recommended Operating Conditions (2)
Input Voltage ................................... 6.5V to 32V
Operating Temperature .............–40°C to +85°C
TOP VIEW
BS
IN
1
2
3
4
8
7
6
5
REF
EN
SW
GND
COMP
FB
MP1591_PD01-SOIC8/N
EXPOSED PAD
ON BACKSIDE
(SOIC8N ONLY)
CONNECT TO PIN 4
Thermal Resistance (3)
θJA
θJC
SOIC8 (w/ Exposed Pad) .......50...... 10... °C/W
SOIC8.....................................90...... 45... °C/W
Part Number*
Package
Temperature
–40°C to +85°C
–40°C to +85°C
MP1591DN
MP1591DS
SOIC8N
SOIC8
Notes:
1) Exceeding these ratings may damage the device.
2) The device is not guaranteed to function outside of its
operating conditions.
For Tape & Reel, add suffix –Z (eg. MP1591DN–Z)
For Lead Free, add suffix –LF (eg. MP1591DN–LF–Z)
*
3) Measured on approximately 1” square of 1 oz copper.
ELECTRICAL CHARACTERISTICS
VIN = 12V, TA = +25°C, unless otherwise noted.
Parameter
Symbol Condition
Min
Typ
20
Max
35
Units
µA
Shutdown Supply Current
Supply Current
VEN = 0V
VEN = 5V, VFB = 1.4V
6.5V ≤ VIN ≤ 32V, VCOMP < 2V
1.0
1.2
mA
V
Feedback Voltage
1.202 1.230 1.258
400
Error Amplifier Voltage Gain
Error Amplifier Transconductance
High-Side Switch On Resistance (4)
Low-Side Switch On Resistance (4)
High-Side Switch Leakage Current
Current Limit (5)
V/V
µA/V
mꢀ
ꢀ
500
700
120
8.5
0
1100
∆IC = ±10µA
VEN = 0V, VSW = 0V
10
µA
2.5
3.6
4.9
A
Current Sense to COMP
Transconductance
3.5
A/V
Oscillation Frequency
280
330
35
380
KHz
KHz
%
Short Circuit Oscillation Frequency
Maximum Duty Cycle (4)
Minimum Duty Cycle (4)
VFB = 0V
VFB = 1.0V
VFB = 1.5V
90
0
%
EN Shutdown Threshold Voltage
Enable Pull-Up Current
0.8
2.4
1.2
1.8
2.6
250
1.6
V
VEN = 0V
µA
V
EN UVLO Threshold
VEN Rising
2.8
EN UVLO Threshold Hysteresis
mV
MP1591 Rev. 2.1
12/5/2005
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2
TM
MP1591 – 2A, 32V, 330KHz STEP-DOWN CONVERTER
ELECTRICAL CHARACTERISTICS (continued)
VIN = 12V, TA = +25°C, unless otherwise noted.
Parameter
Symbol Condition
Min
Typ
160
5.0
100
30
Max
Units
°C
Thermal Shutdown (4)
REF Voltage
IREF = 0
V
REF Load Regulation (4)
REF Line Regulation (4)
Notes:
∆IREF = 0 to 1mA
IREF = 100µA, VIN = 6.5 to 32V
mV
mV
4) These parameters are guaranteed by design, not production tested.
5) Equivalent output current = 1.5A ≥ 50% Duty Cycle
2.0A ≤ 50% Duty Cycle
Assumes ripple current = 30% of load current.
Slope compensation changes current limit.
PIN FUNCTIONS
Pin # Name Description
1
2
BS
IN
High-Side Gate Drive Boost Input. BS supplies the drive for the high-side N-Channel MOSFET
switch. Connect a 10nF or greater capacitor from SW to BS to power the high-side switch.
Power Input. IN supplies the power to the IC, as well as the step-down converter switches.
Drive IN with a 6.5V to 32V power source. Bypass IN to GND with a suitably large capacitor to
eliminate noise on the input to the IC. See Input Capacitor.
3
SW
Power Switching Output. SW is the switching node that supplies power to the output. Connect
the output LC filter from SW to the output load. Note that a capacitor is required from SW to BS
to power the high-side switch.
4
5
GND Ground. For the MP1591DN, connect the Exposed Pad to pin 4.
FB
Feedback Input. FB senses the output voltage to regulate that voltage. Drive FB with a resistive
voltage divider from the output voltage. The feedback threshold is 1.230V. See Setting the
Output Voltage.
6
COMP Compensation Node. COMP is used to compensate the regulation control loop. Connect a
series RC network from COMP to GND to compensate the regulation control loop. In some
cases, an additional capacitor from COMP to GND is required. See Compensation.
7
8
EN
Enable/UVLO. A voltage greater than 2.8V enables operation. For complete low current
shutdown the EN pin voltage needs to be less than 800mV.
REF Reference Output. REF is the 5V reference voltage output. It can supply up to 1mA to external
circuitry. If used, bypass REF to GND with 10nF or greater capacitor. Leave REF unconnected
if not used.
MP1591 Rev. 2.1
12/5/2005
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3
TM
MP1591 – 2A, 32V, 330KHz STEP-DOWN CONVERTER
OPERATION
The MP1591 is a current mode step-down
regulator. It regulates input voltages from 6.5V
to 32V down to an output voltage as low as
1.230V and is able to supply up to 2A of load
current.
The voltage at COMP is compared to the switch
current measured internally to control the output
voltage. The converter uses an internal
N-Channel MOSFET switch to step-down the
input voltage to the regulated output voltage.
Since the MOSFET requires a gate voltage
greater than the input voltage, a boost capacitor
connected between SW and BS drives the gate.
The capacitor is internally charged while SW is
low. An internal 10ꢀ switch from SW to GND is
used to insure that SW is pulled to GND when
the switch is off to fully charge the BS capacitor.
The MP1591 uses current-mode control to
regulate the output voltage. The output voltage
is measured at FB through a resistive voltage
divider and amplified through the internal error
amplifier. The output current of the
transconductance error amplifier is presented at
COMP where a network compensates the
regulation control system.
2
8
IN
CURRENT
SENSE
AMPLIFIER
5V
INTERNAL
REF
REGULATORS
+
--
OSCILLATOR
SLOPE
COMP
1
3
BS
35/330KHz
CLK
M1
M2
+
--
+
S
R
Q
Q
SW
CURRENT
COMPARATOR
SHUTDOWN
COMPARATOR
--
1.2V
7
EN
LOCKOUT
COMPARATOR
--
+
1.8V
2.60V/
2.35V
+
--
4
GND
0.7V 1.230V
5
--
+
FREQUENCY
FOLDBACK
COMPARATOR
ERROR
AMPLIFIER
6
FB
COMP
MP1591_BD01
Figure 1—Functional Block Diagram
MP1591 Rev. 2.1
12/5/2005
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TM
MP1591 – 2A, 32V, 330KHz STEP-DOWN CONVERTER
APPLICATION INFORMATION
The inductance value can be calculated by the
equation:
COMPONENT SELECTION
Setting the Output Voltage
The output voltage is set using a resistive
voltage divider from the output voltage to FB.
The voltage divider divides the output voltage
down by the ratio:
(VIN − VOUT
)
L1 = VOUT
×
(VIN × f × ∆I)
Where VIN is the input voltage, f is the switching
frequency and ꢁI is the peak-to-peak inductor
ripple current.
R2
VFB = VOUT
×
(R1+ R2)
Table 1 lists a number of suitable inductors
from various manufacturers.
Where VFB is the feedback voltage and VOUT is
the output voltage.
Table 1—Inductor Selection Guide
Thus the output voltage is:
Package
Dimensions
(R1+ R2)
VOUT = 1.230 ×
(mm)
Vendor/
Model
Core
Type
Core
Material
R2
W
L
H
A typical value for R2 can be as high as 100kꢀ,
but 10kꢀ is recommended. Using that value, R1
is determined by:
Sumida
CR75
Open
Open
Ferrite
Ferrite
7.0 7.8 5.5
7.3 8.0 5.2
5.5 5.7 5.5
5.5 5.7 5.5
6.7 6.7 3.0
CDH74
R1 ≅ 8.18 × (VOUT − 1.230)
CDRH5D28 Shielded Ferrite
CDRH5D28 Shielded Ferrite
CDRH6D28 Shielded Ferrite
For example, for a 3.3V output voltage, R2 is
10kꢀ, and R1 is 17kꢀ.
Inductor (L1)
CDRH104R Shielded Ferrite 10.1 10.0 3.0
The inductor is required to supply constant
current to the output load while being driven by
the switched input voltage. A larger value
inductor results in less ripple current that results
in lower output ripple voltage. However, the
larger value inductor has a larger physical size,
higher series resistance, and/or lower
saturation current. Choose an inductor that
does not saturate under the worst-case load
conditions. A good rule to use for determining
the inductance is to allow the peak-to-peak
ripple current in the inductor to be
approximately 30% of the maximum load
current that the IC can provide. Also, make sure
that the peak inductor current (the load current
plus half the peak-to-peak inductor ripple
current) is below the 2.3A minimum current
limit.
Toko
D53LC
Type A
Shielded Ferrite
Shielded Ferrite
5.0 5.0 3.0
7.6 7.6 5.1
D75C
D104C
Shielded Ferrite 10.0 10.0 4.3
D10FL
Open
Ferrite
9.7 1.5 4.0
Coilcraft
DO3308
DO3316
Open
Open
Ferrite
Ferrite
9.4 13.0 3.0
9.4 13.0 5.1
Input Capacitor (C1)
The input current to the step-down converter is
discontinuous, and so a capacitor is required to
supply the AC current to the step-down
converter while maintaining the DC input
voltage. A low ESR capacitor is required to
keep the noise at the IC to a minimum. Ceramic
capacitors are preferred, but tantalum or low
ESR electrolytic capacitors may also suffice.
MP1591 Rev. 2.1
12/5/2005
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5
TM
MP1591 – 2A, 32V, 330KHz STEP-DOWN CONVERTER
The input capacitor value should be greater
than 10µF. The capacitor can be electrolytic,
tantalum or ceramic. However, since it absorbs
the input switching current it requires an
adequate ripple current rating. Its RMS current
rating should be greater than approximately 1/2
of the DC load current.
Output Rectifier Diode (D1)
The output rectifier diode supplies the current to
the inductor when the high-side switch is off. To
reduce losses due to the diode forward voltage
and recovery times, use a Schottky rectifier.
Table 2 provides some recommended Schottky
rectifiers based on the maximum input voltage
and current rating.
For insuring stable operation C1 should be
placed as close to the IC as possible.
Alternately, a smaller high quality ceramic
0.1µF capacitor may be placed closer to the IC
and a larger capacitor placed farther away. If
using this technique, it is recommended that the
larger capacitor be a tantalum or electrolytic
type. All ceramic capacitors should be placed
close to the MP1591.
Table 2—Diode Selection Guide
2A Load Current
3A Load Current
VIN
(Max)
Part
Part
Vendor
Vendor
Number
Number
30BQ15
B220
15V
20V
4
1
B320
SK33
1
1, 6
3
SK23
6
SR22
6
SS32
20BQ030
B230
4
B330
1
Output Capacitor (C5)
1
B340L
MBRD330
SK33
1
The output capacitor is required to maintain the
DC output voltage. Low ESR capacitors are
preferred to keep the output voltage ripple low.
The characteristics of the output capacitor also
affect the stability of the regulation control
system. Ceramic, tantalum or low ESR
electrolytic capacitors are recommended. In the
case of ceramic capacitors, the impedance at
the switching frequency is dominated by the
capacitance, and so the output voltage ripple is
mostly independent of the ESR. The output
voltage ripple is estimated to be:
30V
34V
SK23
6
4, 5
1, 6
2, 3
1
SR23
3, 6
2, 3
4
SS23
SS33
21DQ04
MBRS240L
SK24
B340L
MBRS340
SK34
5
4
6
1, 6
2, 3
SS24
2, 3
SS34
Table 3 lists manufacturer’s websites.
Table 3—Schottky Diode Manufacturers
#
1
2
3
4
5
6
Vendor
Web Site
Diodes, Inc.
www.diodes.com
2
⎛
⎜
⎜
⎝
⎞
⎟
⎟
⎠
fLC
VRIPPLE ≅ 1.4 × VIN
×
Fairchild Semiconductor www.fairchildsemi.com
General Semiconductor www.gensemi.com
fSW
Where VRIPPLE is the output ripple voltage, fLC is
the resonant frequency of the LC filter, fSW is the
switching frequency.
International Rectifier
On Semiconductor
Pan Jit International
www.irf.com
www.onsemi.com
www.panjit.com.tw
In the case of tantalum or low-ESR electrolytic
capacitors, the ESR dominates the impedance
at the switching frequency, and so the output
ripple is calculated as:
Choose a rectifier whose maximum reverse
voltage rating is greater than the maximum
input voltage, and whose current rating is
greater than the maximum load current.
VRIPPLE ≅ ∆I× RESR
Where VRIPPLE is the output voltage ripple and
RESR is the equivalent series resistance of the
output capacitors.
MP1591 Rev. 2.1
12/5/2005
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TM
MP1591 – 2A, 32V, 330KHz STEP-DOWN CONVERTER
Compensation
The system crossover frequency fC, (the
frequency where the loop gain drops to 1, or
0dB) is important. A good rule of thumb is to set
the crossover frequency to approximately one
tenth of the switching frequency. In this case,
the switching frequency is 330KHz, so use a
crossover frequency of 33KHz. Lower
crossover frequencies result in slower response
and worse transient load recovery. Higher
crossover frequencies can result in instability.
The system stability is controlled through the
COMP pin. COMP is the output of the internal
transconductance error amplifier. A series
capacitor-resistor combination sets a pole-zero
combination to control the characteristics of the
control system. The DC loop gain is:
VREF
AVDC
=
× AVEA × GCS × RLOAD
VOUT
Where VREF is the feedback threshold voltage,
1.230V, AVEA is the transconductance error
amplifier voltage gain, 400 V/V, and GCS is the
current sense gain (roughly the output current
divided by the voltage at COMP), 3.5 A/V.
Choosing the Compensation Components
The values of the compensation components
given in Table 4 yield a stable control loop for
the output voltage and given capacitor.
Table 4—Compensation Values for Typical
Output Voltage/Capacitor Combinations
The system has 2 poles of importance; one is
due to the compensation capacitor (C4) and the
other is due to the output capacitor (C5). These
are:
VOUT
2.5V
3.3V
5V
C5
R3
C3
C4
22µF Ceramic
22µF Ceramic
22µF Ceramic
22µF Ceramic
47µF SP-Cap
47µF SP-Cap
47µF SP-Cap
47µF SP-Cap
3.9kꢀ
5.1kꢀ
7.5kꢀ
18kꢀ
8.2kꢀ
10kꢀ
16kꢀ
36kꢀ
None
None
None
None
None
None
None
None
4.7nF
3.9nF
2.7nF
1.2nF
2.2nF
2.2nF
1.5nF
1nF
GMEA
fP1
=
(2π × AVEA × C4)
12V
2.5V
3.3V
5V
Where fP1 is the first pole, and GMEA is the error
amplifier transconductance (770µS) and
1
fP2
=
(2π × RLOAD × C5)
12V
The system has one zero of importance due to
the compensation capacitor (C4) and the
compensation resistor (R3) which is
560µF/6.3V, AL
30mꢀ ESR
2.5V
3.3V
5V
100kꢀ
120kꢀ
150kꢀ
180kꢀ
150pF
120pF
82pF
1nF
1nF
1nF
1nF
560µF/6.3V, AL
30mꢀ ESR
1
fZ1
=
470µF/10V, AL
30mꢀ ESR
(2π × R3 × C4)
220µF/25V, AL
30mꢀ ESR
If large value capacitors with relatively high
equivalent-series-resistance (ESR) are used,
the zero due to the capacitance and ESR of the
output capacitor can be compensated by a third
pole set by R3 and C3
12V
33pF
Note: “AL” = Electrolytic
1
fP3
=
(2π × R3 × C3)
MP1591 Rev. 2.1
12/5/2005
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TM
MP1591 – 2A, 32V, 330KHz STEP-DOWN CONVERTER
To optimize the compensation components that
are not listed in Table 4, use the following
procedure.
Example:
VOUT = 5V, C5 = 22µF Ceramic (ESR = 10mꢀ)
R3 ≈ 6.88x107 (22x10-6) (5) = 7568ꢀ
Choose the compensation resistor to set the
desired crossover frequency. Determine the
value by the following equation:
Use the nearest standard value of 7.5kꢀ.
C4 > 1.93x10-5 / 7.5K = 2.57nF
Use standard value of 2.7nF.
2π × C5 × VOUT × fC
R3 =
GEA × GCS × VREF
8π x C5 x RESR x fC = 0.22, which is less than 1.
Therefore, no second compensation capacitor
(C3) is required.
Putting in the know constants and setting the
crossover frequency to the desired 33KHz:
R3 ≅ 6.88 ×107 × C5 × VOUT
External Bootstrap Diode
It is recommended that an external bootstrap
diode be added when the system has a 5V
fixed input or the power supply generates a 5V
output. This helps improve the efficiency of the
regulator. The bootstrap diode can be a low
cost one such as IN4148 or BAT54.
Choose the compensation capacitor to set the
zero below one fourth of the crossover
frequency. Determine the value by the following
equation:
2
1.93 ×10−5
C4 >
≈
5V
π × R3 × fC
R3
Determine if the second compensation
capacitor, C3, is required. It is required if the
ESR zero of the output capacitor occurs at less
than four times the crossover frequency, or
BS
10nF
MP1591
SW
8π × C5 × RESR × fC ≥ 1
MP1591_F02
If this is the case, then add the second
compensation resistor. Determine the value by
the equation:
Figure 2—External Bootstrap Diode
This diode is also recommended for high duty
VOUT
cycle operation (when
>65%) and high
C5 × RESR(MAX)
VIN
C3 =
R3
output voltage (VOUT>12V) applications.
Where RESR(MAX) is the maximum ESR of the
output capacitor.
MP1591 Rev. 2.1
12/5/2005
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TM
MP1591 – 2A, 32V, 330KHz STEP-DOWN CONVERTER
TYPICAL APPLICATION CIRCUITS
C2
10nF
INPUT
6.5V to 32V
2
1
IN
BS
OUTPUT
2.5V
2A
7
3
EN
SW
OFF ON
MP1591
D1
8
5
OPEN
REF
FB
NOT USED
GND
COMP
4
6
C4
4.7nF
C3
OPEN
MP1591_F03
Figure 3—MP1591 with Murata 22µF / 10V Ceramic Output Capacitor
C2
10nF
INPUT
6.5V to 32V
2
1
IN
BS
OUTPUT
2.5V
2A
7
8
3
5
EN
SW
OFF ON
MP1591
D1
OPEN
NOT USED
REF
GND
FB
COMP
4
6
C4
2.2nF
C3
OPEN
MP1591_F04
Figure 4—MP1591 with Panasonic 47µF / 6.3V Special Polymer Output Capacitor
MP1591 Rev. 2.1
12/5/2005
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TM
MP1591 – 2A, 32V, 330KHz STEP-DOWN CONVERTER
PACKAGE INFORMATION
SOIC8 OR SOIC8N (WITH EXPOSED PAD)
PIN 1 IDENT.
0.229(5.820)
0.244(6.200)
0.0075(0.191)
0.0098(0.249)
0.150(3.810)
0.157(4.000)
SEE DETAIL "A"
NOTE 2
0.110(2.794)
0.150(3.810)
0.011(0.280)
0.020(0.508)
x 45o
0.013(0.330)
0.020(0.508)
0.050(1.270)BSC
0.189(4.800)
0.197(5.004)
0o-8o
0.016(0.410)
0.050(1.270)
DETAIL "A"
0.049(1.250)
0.060(1.524)
0.053(1.350)
0.068(1.730)
SEATING PLANE
0.001(0.030)
0.004(0.101)
NOTE:
1) Control dimension is in inches. Dimension in bracket is millimeters.
2) Heat Slug Option Only (N Package)
NOTICE: The information in this document is subject to change without notice. Please contact MPS for current specifications.
Users should warrant and guarantee that third party Intellectual Property rights are not infringed upon when integrating MPS
products into any application. MPS will not assume any legal responsibility for any said applications.
MP1591 Rev. 2.1
12/5/2005
www.MonolithicPower.com
MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited.
© 2005 MPS. All Rights Reserved.
10
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