ADC08D1520WGFQV
更新时间:2024-09-18 08:12:14
品牌:NSC
描述:Low Power, 8-Bit, Dual 1.5 GSPS or Single 3.0 GSPS A/D Converter
ADC08D1520WGFQV 概述
Low Power, 8-Bit, Dual 1.5 GSPS or Single 3.0 GSPS A/D Converter 低功耗, 8位,双路1.5 GSPS或单3.0 GSPS A / D转换器
ADC08D1520WGFQV 数据手册
通过下载ADC08D1520WGFQV数据手册来全面了解它。这个PDF文档包含了所有必要的细节,如产品概述、功能特性、引脚定义、引脚排列图等信息。
PDF下载March 6, 2008
ADC08D1520QML
Low Power, 8-Bit, Dual 1.5 GSPS or Single 3.0 GSPS A/D
Converter
General Description
Features
The ADC08D1520QML is an 8–Bit, dual channel, low power,
high performance CMOS analog-to-digital converter that
builds upon the ADC08D1000 platform. The AD-
C08D1520QML digitizes signals to 8 bits of resolution at
sample rates up to 1.7 GSPS. It has expanded features com-
pared to the ADC08D1000, which include a test pattern output
for system debug, clock phase adjust, and selectable output
demultiplexer modes. Consuming a typical 2.0W in Demulti-
plex Mode at 1.5 GSPS from a single 1.9 Volt supply, this
device is guaranteed to have no missing codes over the full
operating temperature range. The unique folding and inter-
polating architecture, the fully differential comparator design,
the innovative design of the internal sample-and-hold ampli-
fier and the self-calibration scheme enable a very flat re-
sponse of all dynamic parameters beyond Nyquist, producing
a high 7.2 Effective Number of Bits (ENOB) with a 748 MHz
input signal and a 1.5 GHz sample rate while providing a
10-18 Code Error Rate (C.E.R.) Output formatting is offset bi-
nary and the Low Voltage Differential Signaling (LVDS) digital
outputs are compatible with IEEE 1596.3-1996, with the ex-
ception of an adjustable common mode voltage between 0.8V
and 1.2V.
Single +1.9V ±0.1V Operation
■
■
■
■
Interleave Mode for 2x Sample Rate
Multiple ADC Synchronization Capability
Adjustment of Input Full-Scale Range, Offset and Clock
Phase Adjustment
Choice of SDR or DDR output clocking
■
■
■
■
■
■
1:1 or 1:2 Selectable Output Demux
Second DCLK output
Duty Cycle Corrected Sample Clock
Test pattern
Serial Interface for Extended Control
Key Specifications
Resolution
8 Bits
1.5 GSPS (min)
10-18 (typ)
7.2 Bits (typ)
±0.15 LSB (typ)
300 krad(Si)
■
■
■
■
■
■
■
■
Max Conversion Rate
Code Error Rate
ENOB @ 748 MHz Input
DNL
Total Ionizing Dose
Single Event Latch-up
120 MeV-cm2/mg
Each converter has a selectable output demultiplexer which
feeds two LVDS buses. If the 1:2 Demultiplexed Mode is se-
lected, the output data rate is reduced to half the input sample
rate on each bus. When Non-Demultiplexed Mode is select-
ed, that output data rate on channels DI and DQ are at the
same rate as the input sample clock. The two converters can
be interleaved and used as a single 3 GSPS ADC.
Power Consumption
Operating in 1:2 Demux Output
Power Down Mode
2.0 W (typ)
2.9 mW (typ)
—
—
Applications
Direct RF Down Conversion
■
■
■
■
The converter typically consumes less than 2.9 mW in the
Power Down Mode and is available in a 128-pin, thermally
enhanced, multi-layer ceramic quad package and operates
over the Military (-55°C ≤ TA ≤ +125°C) temperature range.
Digital Oscilloscopes
Communications Systems
Test Instrumentation
Ordering Information
NS Part Number
SMD Part Number
NS Package Number
Package Discription
128L, CERQUAD
ADC08D1520WG-QV
5962–0721401VZC
EM128A
GULLWING
ADC08D1520WGFQV
5962F0721401VZC
300 krad(Si)
EM128A
128L, CERQUAD
GULLWING
© 2008 National Semiconductor Corporation
300247
www.national.com
Block Diagram
30024753
www.national.com
2
Pin Configuration
30024701
Note: The exposed pad on the bottom of the package must be soldered to a ground plane to ensure rated performance.
3
www.national.com
Pin Descriptions and Equivalent Circuits
Pin Functions
Pin No.
Symbol
Equivalent Circuit
Description
Output Voltage Amplitude and Serial Interface Clock. Tie this
pin high for normal differential DCLK and data amplitude.
Ground this pin for a reduced differential output amplitude
and reduced power consumption. See 1.1.6 The LVDS
Outputs. When the extended control mode is enabled, this
pin functions as the SCLK input which clocks in the serial
data. See 1.2 NON-EXTENDED CONTROL/EXTENDED
CONTROL for details on the extended control mode. See
1.3 THE SERIAL INTERFACE for description of the serial
interface.
3
OutV / SCLK
A logic high on the PDQ pin puts only the Q-Channel ADC
into the Power Down mode.
29
PDQ
DCLK Edge Select, Double Data Rate Enable and Serial
Data Input. This input sets the output edge of DCLK+ at
which the output data transitions. See 1.1.5.2 OutEdge and
Demultiplex Control Setting When this pin is connected to
1/2 the supply voltage,VA/2, DDR clocking is enabled. When
the Extended Control Mode is enabled, this pin functions as
the SDATA input. See 1.2 NON-EXTENDED CONTROL/
EXTENDED CONTROL for details on the Extended Control
Mode. See 1.3 THE SERIAL INTERFACE for description of
the serial interface.
OutEdge / DDR /
SDATA
4
DCLK Reset. When single-ended DCLK_RST is selected by
setting pin 52 logic high or to VA/2, a positive pulse on this
pin is used to reset and synchronize the DCLK outputs of
multiple converters. See 1.5 MULTIPLE ADC
SYNCHRONIZATION for detailed description. When
differential DCLK_RST is selected by setting pin 52 logic low,
this pin receives the positive polarity of a differential pulse
signal used to reset and synchronize the DCLK outputs of
multiple converters.
DCLK_RST/
DCLK_RST+
15
Power Down Pins. A logic high on the PD pin puts the entire
device into the Power Down Mode.
26
30
PD
Calibration Cycle Initiate. A minimum tCAL_L input clock
cycles logic low followed by a minimum of tCAL_H input clock
cycles high on this pin initiates the calibration sequence. See
2.5.2 Calibration for an overview of calibration and 2.5.2.1
Initiating Calibration for a description of calibration.
CAL
Full Scale Range Select, Alternate Extended Control Enable
and DCLK_RST-. This pin has two functions. It can
conditionally control the ADC full-scale voltage, or become
the negative polarity signal of a differential pair in differential
DCLK_RST Mode. If pin 52 and pin 41 are connected at logic
high, this pin can be used to set the full-scale-range. When
used as the FSR pin, a logic low on this pin sets the full-scale
differential input range to a reduced VIN input level. A logic
high on this pin sets the full-scale differential input range to
Higher VIN input level. See Converter Electrical
14
FSR/DCLK_RST-
Characteristics. When pin 52 is held at logic low, this pin acts
as the DCLK_RST- pin. When in differential DCLK_RST
Mode, there is no pin-controlled FSR and the full-scale-range
is defaulted to the higher VIN input level.
www.national.com
4
Pin Functions
Pin No.
Symbol
Equivalent Circuit
Description
Dual Edge Sampling and Serial Interface Chip Select. With
pin 41 logic low, the device is in Extended Control Mode and
this pin is the enable pin for the Serial Interface . When in
Non-Extended Control Mode and this pin is connected to
VA/2, DES Mode is selected where the I- Channel input is
sampled at twice the input clock rate and the Q- Channel
input is ignored. See 1.1.5.1 Dual-Edge Sampling. When in
Non-Extended Controll Mode and DES is not desired, this
pin should be tied to VA.
127
DES / SCS
LVDS Clock input pins for the ADC. The differential clock
signal must be a.c. coupled to these pins. The input signal is
sampled on the falling edge of CLK+. See 1.1.2 Acquiring
the Input for a description of acquiring the input and 2.4 THE
CLOCK INPUTS for an overview of the clock inputs.
18
19
CLK+
CLK-
Analog signal inputs to the ADC. These differential input
signals must be a.c. coupled to these pins. The differential
full-scale input range is programmable using the FSR pin 14
in Non-Extended Control Mode and the Input Full-Scale
Voltage Adjust register in the Extended Control Mode. Refer
to the VIN specification in the Converter Electrical
Characteristics for the full-scale input range in the Non-
Extended Control Mode. Refer to 1.4 REGISTER
DESCRIPTION for the full-scale input range in the Extended
Control Mode.
VINI−
VINI+
10
11
.22
23
VINQ+
VINQ−
Bandgap output voltage. This pin is capable of sourcing or
VBG
31
sinking 100 μA and can drive a load up to 80 pF.
Calibration Running indication. This pin is at a logic high
when calibration is running.
126
CalRun
External bias resistor connection. Nominal value is 3.3 kΩ
(±0.1%) to ground. See 1.1.1 Calibration.
REXT
32
5
www.national.com
Pin Functions
Pin No.
Symbol
Equivalent Circuit
Description
Temperature Diode Positive (Anode and Negative
(Cathode). This pin is used for die temperature
measurements. See 2.7.2 Thermal Management.
34
35
Tdiode_P
Tdiode_N
Extended Control Enable. This pin always enables or
disables Extended Control Mode. When this pin is set logic
high, the Extended Control Mode is inactive and all control
of the device must be through control pins only . When it is
set logic low, the Extended Control Mode is active. This pin
overrides the Extended Control Enable signal set using pin
14.
41
ECE
DCLK_RST select. This pin selects whether the DCLK is
reset using a single-ended or differential signal. When this
pin is connected at logic high, the DCLK_RST operation is
single-ended and pin 14 functions as FSR/ALT_ECE. When
this pin is logic low, the DCLK_RST operation becomes
differential with functionality on pin 15 (DCLK_RST+) and pin
14 (DCLK_RST-). When in differential DCLK_RST Mode,
there is no pin-controlled FSR and the full-scale-range is
defaulted to 870mV. When pin 41 is set logic low, the
Extended Control Mode is active and the Full-Scale Voltage
Adjust registers can be programmed.
52
DRST_SEL
www.national.com
6
Pin Functions
Pin No.
Symbol
Equivalent Circuit
Description
83 / 78
84 / 77
85 / 76
86 / 75
89 / 72
90 / 71
91 / 70
92 / 69
93 / 68
94 / 67
95 / 66
96 / 65
100 / 61
101 / 60
102 / 59
103 / 58
DI7− / DQ7−
DI7+ / DQ7+
DI6− / DQ6−
DI6+ / DQ6+
DI5− / DQ5−
DI5+ / DQ5+
DI4− / DQ4−
DI4+ / DQ4+
DI3− / DQ3−
DI3+ / DQ3+
DI2− / DQ2−
DI2+ / DQ2+
DI1− / DQ1−
DI1+ / DQ1+
DI0− / DQ0−
DI0+ / DQ0+
I- and Q- channel LVDS Data Outputs that are not delayed
in the output demultiplexer. Compared with the DId and DQd
outputs, these outputs represent the later time samples.
These outputs should always be terminated with a 100Ω
differential resistor.
104 / 57
105 / 56
106 / 55
107 / 54
111 / 50
112 / 49
113 / 48
114 / 47
115 / 46
116 / 45
117 / 44
118 / 43
122 / 39
123 / 38
124 / 37
125 / 36
DId7− / DQd7−
DId7+ / DQd7+
DId6− / DQd6−
DId6+ / DQd6+
DId5− / DQd5−
DId5+ / DQd5+
DId4− / DQd4−
DId4+ / DQd4+
DId3− / DQd3−
DId3+ / DQd3+
DId2− / DQd2−
DId2+ / DQd2+
DId1− / DQd1−
DId1+ / DQd1+
DId0− / DQd0−
DId0+ / DQd0+
I- and Q- channel LVDS Data Outputs that are delayed by
one CLK cycle in the output demultiplexer. Compared with
the DI and DQ outputs, these outputs represent the earlier
time sample. These outputs should always be terminated
with a 100Ω differential resistor. In Non Demux Mode, these
outputs are disabled and are high impedance. When
disabled, these outputs must be left floating.
Out Of Range output. A differential high at these pins
indicates that the differential input is out of range ±VIN/2 as
programmed by the FSR pin in Non-Extended Control Mode
or the Input Full-Scale Voltage Adjust register setting in the
Extended Control Mode). DCLK2 is the exact mirror of DCLK
and should output the same signal at the same rate.
79
80
OR+/DCLK2+
OR-/DCLK2-
Data Clock. Differential Clock outputs used to latch the
output data. Delayed and non-delayed data outputs are
supplied synchronous to this signal. In 1:2 Demultiplexed
Mode, this signal is at 1/2 the input clock rate in SDR Mode
and at 1/4 the input clock rate in the DDR Mode. By default,
the DCLK outputs are not active during the termination
resistor trim section of the calibration cycle. If a system
requires DCLK to run continuously during a calibration cycle,
the termination resistor trim portion of the cycle can be
disabled by setting the Resistor Trim Disable (RTD) bit to
logic high in the Extended Configuration Register (address
9h). This disables all subsequent termination resistor trims
after the initial trim which occurs during the power on
calibration. Therefore, this output is not recommended as a
system clock unless the resistor trim is disabled. When the
device is in the Non-Demultiplexed Mode, DCLK can only be
in DDR Mode and the signal is at 1/2 the input clock rate.
81
82
DCLK-
DCLK+
7
www.national.com
Pin Functions
Pin No.
Symbol
Equivalent Circuit
Description
2, 5, 8, 13,
16, 17, 20,
25, 28, 33,
128
VA
Analog power supply pins. Bypass these pins to ground.
40, 51, 62,
73, 88, 99,
110, 121
Output Driver power supply pins. Bypass these pins to DR
GND.
VDR
1, 6, 7, 9,
12, 21, 24,
27
Ground return for VA.
GND
42, 53, 64,
74, 87, 97,
108, 119
Ground return for VDR
.
DR GND
NC
63, 98, 109,
120
No Connection. Make no connection to these pins.
www.national.com
8
Absolute Maximum Ratings
(Notes 1, 2)
Operating Ratings (Notes 1, 2)
Ambient Temperature Range
−55°C ≤TA ≤+125°C
VA/2 Tolerance for supply 1.9V
Supply Voltage (VA)
650mV ≥VA/2 ≤1.2V
Supply Voltage (VA, VDR
)
2.2V
+1.8V to +2.0V
Supply Difference
VDR - VA
0V to 100 mV
−0.15V to (VA +0.15V)
Driver Supply Voltage (VDR
VIN+, VIN- Voltage Range
)
+1.8V to VA
Voltage on Any Input Pin
200mV to VA
(Maintaining Common Mode)
Ground Difference
(|GND - DR GND|)
CLK Pins Voltage Range
Differential CLK Amplitude
Ground Difference
|GND - DR GND|
Input Current at Any Pin (Note 3)
Package Input Current (Note 3)
Junction Temperature
0V to 100 mV
±25 mA
0V
0V to VA
±50 mA
0.4VP-P to 2.0VP-P
≤ 175°C
ESD Susceptibility (Note 4)
Human Body Model
ꢀ
Package Thermal Resistance
Class 3A (6000V)
θJC
Top of
Package
θJC
Thermal
Pad
Storage Temperature
−65°C to +175°C
Package
θJA
128L Cer Quad
Gullwing
11.5°C/ W
3.8°C/ W
2.0°C/ W
Soldering
process
must
comply
with
National
Semiconductor’s Reflow Temperature Profile specifications.
Refer to www.national.com/packaging.
Quality Conformance Inspection
MIL-STD-883, Method 5005 - Group A
Subgroup
Description
Temp ( C)
+25
1
2
Static tests at
Static tests at
+125
-55
3
Static tests at
4
Dynamic tests at
Dynamic tests at
Dynamic tests at
Functional tests at
Functional tests at
Functional tests at
Switching tests at
Switching tests at
Switching tests at
Setting time at
+25
5
+125
-55
6
7
+25
8A
8B
9
+125
-55
+25
10
11
12
13
14
+125
-55
+25
Setting time at
+125
-55
Setting time at
9
www.national.com
ADC08D1520QML Converter Electrical Characteristics
DC Parameters (Note 14)
The following specifications apply after calibration for VA = VDR = +1.9V; OutV = 1.9V; VIN FSR (a.c. coupled) = differential 870
mVP-P; CL = 10 pF; Differential, a.c. coupled Sine Wave Input Clock, fCLK = 1.5 GHz at 0.5 VP-P with 50% duty cycle; VBG = Floating;
Non-Extended Control Mode; SDR Mode; REXT = 3300 Ω ±0.1%; Analog Signal Source Impedance = 100 Ω Differential; 1:2 Output
Demultiplex, duty cycle stabilizer on. Boldface limits apply for TA = TMIN to TMAX. All other limits TA = 25°C, unless otherwise
noted. (Notes 5, 6)
Typical
(Note 7)
Sub-
groups
Symbol
Parameter
Conditions
Notes
Min
Max
Units
STATIC CONVERTER CHARACTERISTICS
Integral Non-Linearity
(Best fit)
DC Coupled, 1 MHz Sine Wave
Overanged
INL
±0.3
±.9
±.6
LSB
LSB
1, 2, 3
1, 2, 3
DC Coupled, 1 MHz Sine Wave
Overanged
DNL
Differential Non-Linearity
±0.15
Resolution with No Missing
Codes
8
Bits
LSB
mV
1, 2, 3
1, 2, 3
1, 2, 3
VOFF
Offset Error
−0.55
−0.6
−1.5
1.5
±25
(Note
8)
PFSE
Positive Full-Scale Error
(Note
8)
NFSE
Negative Full-Scale Error
−1.31
±25
mV
1, 2, 3
ANALOG INPUT AND REFERENCE CHARACTERISTICS
mVP-P
mVP-P
mVP-P
mVP-P
530
840
94
1, 2, 3
1, 2, 3
1, 2, 3
1, 2, 3
1, 2, 3
1, 2, 3
FSR pin 14 Low
600
900
100
650
960
106
Full Scale Analog
VIN
Differential Input Range
FSR pin 14 High
Ω
Ω
Differential Input
RIN
Resistance
ANALOG OUTPUT CHARACTERISTICS
1.20
V
V
1, 2, 3
1, 2, 3
Bandgap Reference
Output Voltage
VBG
IBG = ±100 µA
1.26
1.33
CLOCK INPUT CHARACTERISTICS
VP-P
VP-P
VP-P
VP-P
.5
.5
1, 2, 3
1, 2, 3
1, 2, 3
1, 2, 3
Sine Wave Clock
0.6
0.6
2.0
2.0
Differential Clock Input
Level
VID
Square Wave Clock
DIGITAL CONTROL PIN CHARACTERISTICS
0.85 x
VA
VIH
VIL
Logic High Input Voltage
Logic Low Input Voltage
V
V
1, 2, 3
1, 2, 3
0.15 x
VA
DIGITAL OUTPUT CHARACTERISTICS
Measured differentially,
mVP-P
mVP-P
mVP-P
mVP-P
580
380
1, 2, 3
1, 2, 3
1, 2, 3
1, 2, 3
(Note
13)
780
590
OutV = VA, VBG = Floating
920
720
LVDS Differential Output
Voltage
VOD
Measured differentially,
(Note
13)
OutV = GND, VBG = Floating
www.national.com
10
Typical
(Note 7)
Sub-
groups
Symbol
Parameter
Conditions
Notes
Min
Max
Units
POWER SUPPLY CHARACTERISTICS
1:2 Demux Output
ꢀ
ꢀ
ꢀ
PD = PDQ = Low
PD = Low, PDQ = High
PD = PDQ = High
1, 2, 3
1, 2, 3
820
565
1.5
875
615
mA (max)
mA (max)
mA
IA
Analog Supply Current
1:2 Demux Output
PD = PDQ = Low
PD = Low, PDQ = High
PD = PDQ = High
ꢀ
230
125
ꢀ
290
170
ꢀ
Output Driver Supply
Current
1, 2, 3
1, 2, 3
mA (max)
mA (max)
mA
IDR
0.018
1:2 Demux Output
PD = PDQ = Low
PD = Low, PDQ = High
PD = PDQ = High
ꢀ
2
1.3
2.9
ꢀ
2.2
1.49
ꢀ
1, 2, 3
1, 2, 3
W (max)
W (max)
mW
PD
Power Consumption
AC Parameters (Note 14)
Typical
(Note 7)
Sub-
groups
Symbol
Parameter
Conditions
Notes
Min
Max
Units
Non-DES MODE DYNAMIC CONVERTER CHARACTERISTICS, 1:2 DEMUX MODE
fIN = 373 MHz, VIN = FSR − 0.5 dB
fIN = 748 MHz, VIN = FSR − 0.5 dB
fIN = 373 MHz, VIN = FSR − 0.5 dB
fIN = 748 MHz, VIN = FSR − 0.5 dB
fIN = 373 MHz, VIN = FSR − 0.5 dB
fIN = 748 MHz, VIN = FSR − 0.5 dB
fIN = 373 MHz, VIN = FSR − 0.5 dB
fIN = 748 MHz, VIN = FSR − 0.5 dB
fIN = 373 MHz, VIN = FSR − 0.5 dB
fIN = 748 MHz, VIN = FSR − 0.5 dB
(VIN+) − (VIN−) > + Full Scale
7.4
7.2
7
Bits (min)
Bits (min)
dB (min)
dB (min)
dB (min)
dB (min)
dB (max)
dB (max)
dB (min)
dB (min)
4, 5, 6
4, 5, 6
4, 5, 6
4, 5, 6
4, 5, 6
4, 5, 6
4, 5, 6
4, 5, 6
4, 5, 6
4, 5, 6
4, 5, 6
4, 5, 6
ENOB
SINAD
SNR
Effective Number of Bits
46.3
45.4
47
43.9
43.9
Signal-to-Noise Plus
Distortion Ratio
Signal-to-Noise Ratio
45
−53.4
−53
55.5
53
−47.5
THD
Total Harmonic Distortion
47.5
Spurious-Free dynamic
Range
SFDR
255
0
Out of Range Output Code
(VIN+) − (VIN−) < − Full Scale
INTERLEAVE MODE (DES Pin 127=VA/2) - DYNAMIC CONVERTER CHARACTERISTICS, 1:4 DEMUX MODE
fIN = 373 MHz, VIN = FSR − 0.5 dB
ENOB
Effective Number of Bits
7.0
6.6
Bits
dB
4, 5, 6
4, 5, 6
Signal to Noise Plus
Distortion Ratio
fIN = 373 MHz, VIN = FSR − 0.5 dB
SINAD
44
41.5
41.5
fIN = 373 MHz, VIN = FSR − 0.5 dB
fIN = 373 MHz, VIN = FSR − 0.5 dB
SNR
THD
Signal to Noise Ratio
44
dB
dB
4, 5, 6
4, 5, 6
Total Harmonic Distortion
−55
−45.2
Spurious Free Dynamic
Range
fIN = 373 MHz, VIN = FSR − 0.5 dB
SFDR
50
44.1
dB
4, 5, 6
11
www.national.com
AC Timing Parameters (Note 14)
Typical
(Note 7)
Sub-
groups
Symbol
Parameter
Conditions
Notes
Min
Max
Units
AC TIMING CHARACTERISTICS
Non-DES Mode or DES Mode in
1:2 Output Demux
1.7
50
1.5
1.0
GHz
GHz
9, 10, 11
9, 10, 11
Maximum Input Clock
Frequency
fCLK(max)
Non-DES Mode or DES Mode in
Non-demux Output
45
%
%
9, 10, 11
9, 10, 11
DCLK Duty Cycle
55
4
CLK±
Cycles
(min)
tPWR
Pulse Width DCLK_RST±
9, 10, 11
CLK±
Cycles
tCAL_L
tCAL_H
CAL Pin Low Time
CAL Pin High Time
See Figure 10
See Figure 10
1280
1280
9, 10, 11
9, 10, 11
CLK±
Cycles
www.national.com
12
Typical Electrical Characteristics
DC Parameters
The following specifications apply after calibration for VA = VDR = +1.9V; OutV = 1.9V; VIN FSR (a.c. coupled) = differential 870
mVP-P; CL = 10 pF; Differential, a.c. coupled Sine Wave Input Clock, fCLK = 1.5 GHz at 0.5 VP-P with 50% duty cycle; VBG = Floating;
Non-Extended Control Mode; SDR Mode; REXT = 3300 Ω ±0.1%; Analog Signal Source Impedance = 100 Ω Differential; 1:2 Output
Demultiplex, duty cycle stabilizer on. Boldface limits apply for TA = TMIN to TMAX. All other limits TA = 25°C, unless otherwise
noted. (Notes 5, 6)
Typical
(Note 7)
Symbol
Parameter
Conditions
Notes
Units
STATIC CONVERTER CHARACTERISTICS
VOFF_ADJ
FS_ADJ
Input Offset Adjustment Range Extended Control Mode
Full-Scale Adjustment Range Extended Control Mode
±45
±20
mV
%FS
ANALOG INPUT AND REFERENCE CHARACTERISTICS
Differential
0.02
1.6
pF
pF
pF
pF
Analog Input Capacitance,
Normal operation
(Note 9)
(Note 9)
Each input pin to ground
Differential
CIN
0.08
2.2
Analog Input Capacitance,
DES Mode
Each input pin to ground
ANALOG OUTPUT CHARACTERISTICS
TA = −55°C to +125°C,
IBG = ±100 µA
Bandgap Reference Voltage
TC VBG
61
80
ppm/°C
pF
Temperature Coefficient
Maximum Bandgap Reference
CLOAD VBG
load Capacitance
TEMPERATURE DIODE CHARACTERISTICS
192 µA vs 12 µA, TJ = 25°C
192 µA vs 12 µA, TJ = 125°C
71.23
94.8
mV
mV
ΔVBE
Temperature Diode Voltage
CHANNEL-TO-CHANNEL CHARACTERISTICS
Offset Match
1
1
LSB
LSB
Positive Full-Scale Match
Negative Full-Scale Match
Phase Matching (I,Q)
Zero offset selected in Control Register
Zero offset selected in Control Register
fIN = 1.0 GHz
1
LSB
< 1
Degree
Crosstalk from I- Channel
(Aggressor) to Q- Channel
(Victim)
Aggressor = 1160 MHz F.S.
Victim = 100 MHz F.S.
X-TALK
X-TALK
−66
−66
dB
dB
Crosstalk from Q- Channel
(Aggressor) to I- Channel
(Victim)
Aggressor = 1160 MHz F.S.
Victim = 100 MHz F.S.
CLOCK INPUT CHARACTERISTICS
II
VIN = 0 or VIN = VA
Differential
Input Current
±1
0.02
1.5
µA
pF
pF
CIN
Input Capacitance
(Note 9)
Each input to ground
DIGITAL CONTROL PIN CHARACTERISTICS
CIN
Input Capacitance
Each input to ground
(Note 11)
1.2
pF
DIGITAL OUTPUT CHARACTERISTICS
Change in LVDS Output Swing
ΔVO DIFF
±1
mV
Between Logic Levels
VOS
VOS
VBG = Floating (See Figure 1)
VBG = VA (See Figure 1)
Output Offset Voltage
Output Offset Voltage
800
mV
mV
(Note 13)
1100
Output Offset Voltage Change
Between Logic Levels
ΔVOS
±1
±4
mV
mA
Output+ & Output− connected to 0.8V,
VBG = Floating, OutV = VA
IOS
Output Short Circuit Current
13
www.national.com
Typical
(Note 7)
Symbol
Parameter
Conditions
Notes
Units
ZO
Differential Output Impedance
CalRun H level output
100
1.72
0.17
Ω
V
V
VOH
VOL
IOH = −400 µA
IOH = 400 µA
(Note 10)
(Note 10)
CalRun L level output
POWER SUPPLY CHARACTERISTICS
Change in Full Scale Error with change in
VA from 1.8V to 2.0V
D.C. Power Supply Rejection
PSRR1
Ratio
30
51
dB
dB
A.C. Power Supply Rejection
248 MHz, 50 mVP-P injected on VA
PSRR2
Ratio
AC Parameters
Typical
(Note 7)
Symbol
Parameter
Conditions
Notes
Units
Non-DES MODE DYNAMIC CONVERTER CHARACTERISTICS, 1:2 DEMUX MODE
FPBW
C.E.R.
Full Power Bandwidth
Code Error Rate
Non-DES Mode
2.0
10−18
±0.5
±1.0
−60
GHz
Error/Sample
dBFS
dBFS
dB
d.c. to 498 MHz
Gain Flatness
d.c. to 1 GHz
fIN = 373 MHz, VIN = FSR − 0.5 dB
fIN = 748 MHz, VIN = FSR − 0.5 dB
fIN = 373 MHz, VIN = FSR − 0.5 dB
fIN = 748 MHz, VIN = FSR − 0.5 dB
2nd Harm
3rd Harm
IMD
Second Harmonic Distortion
Third Harmonic Distortion
Intermodulation Distortion
−55
dB
−62
dB
−58
dB
fIN1 = 365 MHz, VIN = FSR − 7 dB
fIN2 = 375 MHz, VIN = FSR − 7 dB
−50
dB
INTERLEAVE MODE (DES Pin 127=VA/2) - DYNAMIC CONVERTER CHARACTERISTICS, 1:4 DEMUX MODE
FPBW
Full Power Bandwidth
Dual Edge Sampling Mode
1.7
−60
−65
GHz
dB
fIN = 373 MHz, VIN = FSR − 0.5 dB
fIN = 373 MHz, VIN = FSR − 0.5 dB
2nd Harm
3rd Harm
Second Harmonic Distortion
Third Harmonic Distortion
dB
www.national.com
14
AC Timing Parameters
Typical
(Note 7)
Symbol
Parameter
Conditions
Notes
Units
AC TIMING CHARACTERISTICS
Non-DES Mode
DES Mode
200
500
MHz
MHz
fCLK(min)
Minimum Input Clock Frequency
Input Clock Duty Cycle
% (min)
% (max)
% (min)
% (max)
ps (min)
ps (min)
ps
200 MHz ≤ fCLK ≤ 1.5 GHz
(Non-DES Mode)
(Note 10)
(Note 10)
50
50
500 MHz ≤ fCLK ≤ 1.5 GHz
(DES Mode)
tCL
tCH
tSR
tHR
Input Clock Low Time
Input Clock High Time
Setup Time DCLK_RST±
Hold Time DCLK_RST±
(Note 10)
(Note 10)
333
333
90
30
ps
Synchronizing Edge to DCLK
Output Delay
tSD
tOD + tOSK
150
Differential Low-to-High
Transition Time
tLHT
tHLT
10% to 90%, CL = 2.5 pF
10% to 90%, CL = 2.5 pF
ps
ps
Differential High-to-Low
Transition Time
150
50% of DCLK transition to 50% of Data
transition, SDR Mode
tOSK
DCLK-to-Data Output Skew
±50
ps (max)
and DDR Mode, 0° DCLK
tSU
tH
tAD
tAJ
Data-to-DCLK Set-Up Time
DCLK-to-Data Hold Time
Sampling (Aperture) Delay
Aperture Jitter
DDR Mode, 90° DCLK
400
560
1.6
ps
ps
DDR Mode, 90° DCLK
Input CLK+ Fall to Acquisition of Data
ns
0.4
ps rms
Input Clock-to Data Output Delay 50% of Input Clock transition to 50% of Data
tOD
4
ns
(in addition to Pipeline Delay)
transition
DI Outputs
DId Outputs
13
14
Non-DES Mode
DES Mode
13
Pipeline Delay (Latency)
1:2 Demux Mode
(Notes
10, 12)
DQ Outputs
CLK± Cycles
13.5
14
Non-DES Mode
DES Mode
DQd Outputs
14.5
13
DI Outputs
DId Outputs
13
Non-DES Mode
DES Mode
13
Pipeline Delay (Latency)
1:1 Demux Mode
(Notes
10, 12)
DQ Outputs
CLK± Cycles
CLK± Cycle
13.5
13
Non-DES Mode
DES Mode
DQd Outputs
13.5
Differential VIN step from ±1.2V to 0V to get
accurate conversion
Over Range Recovery Time
1
PD low to Rated Accuracy
Conversion (Wake-Up Time)
Non-DES Mode
500
1
ns
µs
tWU
DES Mode
fSCLK
tSSU
tSH
Serial Clock Frequency
15
2.5
1
MHz
Data to Serial Clock Setup Time
Data to Serial Clock Hold Time
Serial Clock Low Time
ns (min)
ns (min)
ns
26
15
www.national.com
Typical
(Note 7)
Symbol
Parameter
Conditions
Notes
Units
Serial Clock High Time
Calibration Cycle Time
26
1.4 x 106
ns
tCAL
CLK± Cycles
Note 1: Absolute Maximum Ratings indicate limits beyond which damage to the device may occur. There is no guarantee of operation at the Absolute Maximum
Ratings. Operating Ratings indicate conditions for which the device is functional, but do not guarantee specific performance limits. For guaranteed specifications
and test conditions, see the Electrical Characteristics. The guaranteed specifications apply only for the test conditions listed. Some performance characteristics
may degrade when the device is not operated under the listed test conditions.
Note 2: All voltages are measured with respect to GND = DR GND = 0V, unless otherwise specified.
Note 3: When the input voltage at any pin exceeds the power supply limits (that is, less than GND or greater than VA), the current at that pin should be limited to
25 mA. The 50 mA maximum package input current rating limits the number of pins that can safely exceed the power supplies with an input current of 25 mA to
two. This limit is not placed upon the power, ground and digital output pins.
Note 4: Human body model is 100 pF capacitor discharged through a 1.5 kΩ resistor.
Note 5: The analog inputs are protected as shown below. Input voltage magnitudes beyond the Absolute Maximum Ratings may damage this device.
30024704
Note 6: To guarantee accuracy, it is required that VA and VDR be well bypassed. Each supply pin must be decoupled with separate bypass capacitors. Additionally,
achieving rated performance requires that the backside exposed pad be well grounded.
Note 7: Typical figures are at TA = 25°C, and represent most likely parametric norms. Test limits are guaranteed to MIL-PRF-38535.
Note 8: Calculation of Full-Scale Error for this device assumes that the actual reference voltage is exactly its nominal value. Full-Scale Error for this device,
therefore, is a combination of Full-Scale Error and Reference Voltage Error. See Figure 2. For relationship between Gain Error and Full-Scale Error, see
Specification Definitions for Gain Error.
Note 9: The analog and clock input capacitances are die capacitances only. Additional package capacitances of 0.65 pF differential and 0.95 pF each pin to
ground are isolated from the die capacitances by lead and bond wire inductances.
Note 10: This parameter is guaranteed by design and/or characterization and is not tested in production.
Note 11: The digital control pin capacitances are die capacitances only. Additional package capacitance of 1.6 pF each pin to ground are isolated from the die
capacitances by lead and bond wire inductances.
Note 12: Each of the two converters of the ADC08D1520QMLQML has two LVDS output buses, which each clock data out at one half the sample rate. The data
at each bus is clocked out at one half the sample rate. The second bus (D0 through D7) has a pipeline latency that is one Input Clock cycle less than the latency
of the first bus (Dd0 through Dd7). 1:2 Demux Mode.
Note 13: Tying VBG to the supply rail will increase the output offset voltage (VOS) by 300mv (typical), as shown in the VOS specification above. Tying VBG to the
supply rail will also affect the differential LVDS output voltage (VOD), causing it to increase by 30mV (typical).
Note 14: Pre and post irradiation limits are identical to those listed under AC and DC electrical characteristics except as listed in the Post Radiation Limits Table.
These parts may be dose rate sensitive in a space environment and demonstrate enhanced low dose rate effect. Radiation end point limits for the noted parameters
are guaranteed only for the conditions as specified in MIL-STD-883, Method 1019
DIFFERENTIAL NON-LINEARITY (DNL) is the measure of
Specification Definitions
the maximum deviation from the ideal step size of 1 LSB.
Measured at sample rate = 500 MSPS with a 1MHz input
sinewave.
APERTURE (SAMPLING) DELAYis the amount of delay,
measured from the sampling edge of the Clock input, after
which the signal present at the input pin is sampled inside the
device.
EFFECTIVE NUMBER OF BITS (ENOB, or EFFECTIVE
BITS) is another method of specifying Signal-to-Noise and
Distortion Ratio, or SINAD. ENOB is defined as (SINAD −
1.76) / 6.02 and says that the converter is equivalent to a per-
fect ADC of this (ENOB) number of bits.
APERTURE JITTER (tAJ) is the variation in aperture delay
from sample to sample. Aperture jitter shows up as input
noise.
CODE ERROR RATE (C.E.R.) is the probability of error and
is defined as the probable number of word errors on the ADC
output per unit of time divided by the number of words seen
in that amount of time.. A C.E.R. of 10-18 corresponds to a
statistical error in one word about every four (4) years.
FULL POWER BANDWIDTH (FPBW) is a measure of the
frequency at which the reconstructed output fundamental
drops 3 dB below its low frequency value for a full-scale input.
GAIN ERROR is the deviation from the ideal slope of the
transfer function. It can be calculated from Offset and Full-
Scale Errors:
CLOCK DUTY CYCLE is the ratio of the time that the clock
waveform is at a logic high to the total time of one clock period.
www.national.com
16
Positive Gain Error = Offset Error − Positive Full-Scale
Error
Negative Gain Error = −(Offset Error − Negative Full-
Scale Error)
OUTPUT DELAY (tOD) is the time delay (in addition to
Pipeline Delay) after the falling edge of CLK+ before the data
update is present at the output pins.
OVER-RANGE RECOVERY TIME is the time required after
the differential input voltages goes from ±1.2V to 0V for the
converter to recover and make a conversion with its rated ac-
curacy.
Gain Error = Negative Full-Scale Error − Positive Full-
Scale Error = Positive Gain Error + Negative Gain Error
INTEGRAL NON-LINEARITY (INL) is a measure of worst
case deviation of the ADC transfer function from an ideal
straight line drawn through the ADC transfer function. The
deviation of any given code from this straight line is measured
from the center of that code value. The best fit method is used.
PIPELINE DELAY (LATENCY) is the number of input clock
cycles between initiation of conversion and when that data is
presented to the output driver stage. New data is available at
every clock cycle, but the data lags the conversion by the
Pipeline Delay plus the tOD
.
INTERMODULATION DISTORTION (IMD) is the creation of
additional spectral components as a result of two sinusoidal
frequencies being applied to the ADC input at the same time.
It is defined as the ratio of the power in the second and third
order intermodulation products to the power in one of the
original frequencies. IMD is usually expressed in dBFS.
POSITIVE FULL-SCALE ERROR (PFSE) is a measure of
how far the last code transition is from the ideal 1-1/2 LSB
below a differential +VIN/2. For the ADC08D1520QML the
reference voltage is assumed to be ideal, so this error is a
combination of full-scale error and reference voltage error.
POWER SUPPLY REJECTION RATIO (PSRR) can be one
of two specifications. PSRR1 (DC PSRR) is the ratio of the
change in full-scale error that results from a power supply
voltage change from 1.8V to 2.0V. PSRR2 (AC PSRR) is a
measure of how well an a.c. signal riding upon the power
supply is rejected from the output and is measured with a 248
MHz, 50 mVP-P signal riding upon the power supply. It is the
ratio of the output amplitude of that signal at the output to its
amplitude on the power supply pin. PSRR is expressed in dB.
LSB (LEAST SIGNIFICANT BIT) is the bit that has the small-
est value or weight of all bits. This value is
VFS / 2N
where VFS is the differential full-scale amplitude VIN as set by
the FSR input and "N" is the ADC resolution in bits, which is
8, for the ADC08D1520QML.
LOW VOLTAGE DIFFERENTIAL SIGNALING (LVDS)
DIFFERENTIAL OUTPUT VOLTAGE (VOD) is the absolute
value of the difference between the VD+ and VD- outputs; each
measured with respect to Ground.
SIGNAL TO NOISE RATIO (SNR) is the ratio, expressed in
dB, of the rms value of the input signal at the output to the rms
value of the sum of all other spectral components below one-
half the sampling frequency, not including harmonics or d.c.
SIGNAL TO NOISE PLUS DISTORTION (S/(N+D) or
SINAD) is the ratio, expressed in dB, of the rms value of the
input signal at the output to the rms value of all of the other
spectral components below half the input clock frequency, in-
cluding harmonics but excluding d.c.
SPURIOUS-FREE DYNAMIC RANGE (SFDR) is the differ-
ence, expressed in dB, between the rms values of the input
signal at the output and the peak spurious signal, where a
spurious signal is any signal present in the output spectrum
that is not present at the input, excluding d.c.
30024746
TOTAL HARMONIC DISTORTION (THD) is the ratio ex-
pressed in dB, of the rms total of the first nine harmonic levels
at the output to the level of the fundamental at the output. THD
is calculated as
FIGURE 1.
LVDS OUTPUT OFFSET VOLTAGE (VOS) is the midpoint
between the D+ and D- pins output voltage with respect to
ground; ie., [(VD+) +( VD-)]/2.
MISSING CODES are those output codes that are skipped
and will never appear at the ADC outputs. These codes can-
not be reached with any input value.
MSB (MOST SIGNIFICANT BIT) is the bit that has the largest
value or weight. Its value is one half of full scale.
where Af1 is the RMS power of the fundamental (output) fre-
quency and Af2 through Af10 are the RMS power of the first 9
harmonic frequencies in the output spectrum.
NEGATIVE FULL-SCALE ERROR (NFSE) is a measure of
how far the first code transition is from the ideal 1/2 LSB above
a differential −VIN/2 with the FSR pin low. For the AD-
C08D1520QML the reference voltage is assumed to be ideal,
so this error is a combination of full-scale error and reference
voltage error.
– Second Harmonic Distortion (2nd Harm) is the differ-
ence, expressed in dB, between the RMS power in the input
frequency seen at the output and the power in its 2nd har-
monic level at the output.
– Third Harmonic Distortion (3rd Harm) is the difference
expressed in dB between the RMS power in the input fre-
quency seen at the output and the power in its 3rd harmonic
level at the output.
OFFSET ERROR (VOFF) is a measure of how far the mid-
scale point is from the ideal zero voltage differential input.
Offset Error = Actual Input causing average of 8k samples to
result in an average code of 127.5.
17
www.national.com
Transfer Characteristic
30024722
FIGURE 2. Input / Output Transfer Characteristic
www.national.com
18
Timing Diagrams
30024714
FIGURE 3. SDR Clocking in 1:2 Demultiplexed Mode
30024759
FIGURE 4. DDR Clocking in 1:2 Demultiplexed and Non-DES Mode
19
www.national.com
30024760
FIGURE 5. DDR Clocking in Non-Demultiplexed and Non-DES Mode
www.national.com
20
30024719
FIGURE 6. Serial Interface Timing
30024720
FIGURE 7. Clock Reset Timing in DDR Mode
30024723
FIGURE 8. Clock Reset Timing in SDR Mode with OUTEDGE Low
21
www.national.com
30024724
FIGURE 9. Clock Reset Timing in SDR Mode with OUTEDGE High
30024725
FIGURE 10. On-Command Calibration Timing
www.national.com
22
Typical Performance Characteristics VA = VDR = 1.9V, fCLK = 1500 MHz, TA= 25°C, 1:2 Demux mode,
Non-DES Mode unless otherwise stated.
INL vs CODE
INL vs TEMPERATURE
DNL vs. TEMPERATURE
ENOB vs. TEMPERATURE
30024764
30024765
30024767
30024776
DNL vs. CODE
30024766
POWER DISSIPATION vs. SAMPLE RATE
30024781
23
www.national.com
ENOB vs. SUPPLY VOLTAGE
ENOB vs. INPUT FREQUENCY
SNR vs. SUPPLY VOLTAGE
ENOB vs. SAMPLE RATE
SNR vs. TEMPERATURE
SNR vs. SAMPLE RATE
30024777
30024779
30024769
30024778
30024768
30024770
www.national.com
24
SNR vs. INPUT FREQUENCY
THD vs. SUPPLY VOLTAGE
THD vs. INPUT FREQUENCY
THD vs. TEMPERATURE
THD vs. SAMPLE RATE
SFDR vs. TEMPERATURE
30024771
30024773
30024775
30024772
30024774
30024785
25
www.national.com
SFDR vs. SUPPLY VOLTAGE
SFDR vs. SAMPLE RATE
30024784
30024782
SFDR vs. INPUT FREQUENCY
Spectral Response at FIN = 373 MHz
30024783
30024787
Spectral Response at FIN = 745 MHz
CROSSTALK vs SOURCE FREQUENCY
30024788
30024763
www.national.com
26
FULL POWER BANDWIDTH
30024786
27
www.national.com
register in the Extended Control Mode. Disabling the input
termination resistor is not recommended for the initial cali-
bration after power-up. The second portion of the calibration
cycle is the ADC calibration in which internal bias currents are
set. The ADC calibration is performed regardless of the RTD
bit setting. Running the calibration is an important part of this
chip’s functionality and is required in order to obtain specified
performance. In addition to the requirement that a calibration
be run at power-up, a calibration must be run whenever the
FSR pin is changed. For best performance, we recommend
that a calibration be run after application of power once the
power supplies have settled and the part temperature has
stabilized. Further calibrations should be run whenever the
operating temperature changes significantly relative to the
specific system performance requirements. See 2.5.2.1 Initi-
ating Calibration for more information. Calibration can not be
initiated or run while the device is in the Power-Down Mode.
See1.1.7 Power Down for information on the interaction be-
tween Power down and calibration.
1.0 Functional Description
The ADC08D1520QML is a versatile A/D Converter with an
innovative architecture permitting very high speed operation.
The controls available ease the application of the device to
circuit solutions. Optimum performance requires adherence
to the provisions discussed here and in the Applications In-
formation Section.
While it is not recommended in radiation environments to al-
low an active pin to float, pins 4, 14, 52 and 127 of the
ADC08D1520QML are designed to be left floating without
jeopardy in non radiation environments. In all discussions
throughout this data sheet, whenever a function is called by
allowing a control pin to float, connecting that pin to a potential
of one half the VA supply voltage is recommended for radia-
tion environments.
1.1 OVERVIEW
The ADC08D1520QML uses a calibrated folding and inter-
polating architecture that achieves over 7.25 effective bits.
The use of folding amplifiers greatly reduces the number of
comparators and power consumption. Interpolation reduces
the number of front-end amplifiers required, minimizing the
load on the input signal and further reducing power require-
ments. In addition to other things, on-chip calibration reduces
the INL bow often seen with folding architectures. The result
is an extremely fast, high performance, low power converter.
In normal operation, calibration should be performed just after
application of power and whenever a valid calibration com-
mand is given. A calibration command can be issued using
two methods. The first method is to hold the CAL pin low for
at least tCAL_L input clock cycles, then hold it high for at least
another tCAL_H input clock cycles as defined in the Converter
Electrical Characteristics. The second method is to program
the CAL bit in the Calibration register. The functionality of the
CAL bit is exactly the same as using the CAL pin. The CAL
bit must be programmed to 0b for tCAL_L input clock cycles and
then programmed to 1b for at least tCAL_H input clock cycles
to initiate a calibration cycle. The time taken by the calibration
procedure is specified as tCAL in the Converter Electrical
Characteristics.
The analog input signal that is within the converter's input
voltage range is digitized to eight bits at speeds of 200 MSPS
to 1.7 GSPS, typical. Differential input voltages below nega-
tive full-scale will cause the output word to consist of all
zeroes. Differential input voltages above positive full-scale
will cause the output word to consist of all ones. Either of
these conditions at either the I- or Q- Channel input will cause
the OR (Out of Range) output to be activated. This single OR
output indicates when the output code from one or both of the
channels is below negative full scale or above positive full
scale.
The CAL bit does not reset itself to zero automatically, but
must be manually reset before another calibration event is
desired, the CAL bit may be left high indefinitely, with no neg-
ative consequences.
The RTD bit setting is critical for running a calibration event
with the Clock Phase Adjust enabled. If initiating a calibration
event while the Clock Phase Adjust is enabled, the RTD bit
must be set to high, or no calibration will occur. If initiating a
calibration event while the Clock Phase Adjust is not enabled,
a normal calibration will occur, regardless of the setting of the
RTD bit.
Each converter has a selectable output demultiplexer which
feeds two LVDS buses. If the 1:2 Demultiplexed Mode is se-
lected, the output data rate is reduced to half the input sample
rate on each bus. When Non-Demultiplexed Mode is select-
ed, that output data rate on channels DI and DQ are at the
same rate as the input sample clock.
The output levels may be selected to be normal or reduced.
Using reduced levels saves power but could result in erro-
neous data capture of some or all of the bits, especially at
higher sample rates and in marginally designed systems.
Calibration Operation Notes:
•
During the calibration cycle, the OR output may be active
as a result of the calibration algorithm. All data on the
output pins and the OR output are invalid during the
calibration cycle.
1.1.1 Calibration
The ADC08D1520QML has a calibration feature which must
be invoked by the user. If the device is powered-up in the
Extended Control Mode, the registers will be in an unknown
state and no calibration is performed. For the initial calibration
after power-up, we recommend that the registers first be pro-
grammed to a known state before performing a calibration or
the part be calibrated in the pin control mode. All subsequent
calibrations can be run in either the Non-Extended Control
Mode or the Extended Control Mode.
•
During the calibration, all clocks are halted on chip,
including internal clocks and DCLK, while the input
termination resistor is trimmed to a value that is equal to
REXT / 33. This is to reduce noise during the input resistor
calibration portion of the calibration cycle. See for
information on maintaining DCLK operation during on-
command calibration.
This external resistor is located between pin 32 and
ground. REXT must be 3300 Ω ±0.1%. With this value, the
input termination resistor is trimmed to be 100 Ω. Because
REXT is also used to set the proper current for the Track
and Hold amplifier, for the preamplifiers and for the
comparators, other values of REXT should not be used.
The calibration algorithm consists of two portions. The first
portion is calibrating the analog input. This calibration trims
the 100 Ω analog input differential termination resistor and
minimizes full-scale error, offset error, DNL and INL, resulting
in maximizing SNR, THD, SINAD (SNDR) and ENOB. This
portion of the calibration can be disabled by programming the
Resistor Trim Disable (RTD) bit in the Extended Configuration
•
The CalRun output is high whenever the calibration
procedure is running. This is true whether the calibration
is done at power-up or on-command.
www.national.com
28
•
It is important that no digital activity take place on any of
the digital input lines during the calibration process, except
that there must be a stable, constant frequency CLK signal
present and that SCLK may be active if the Enhanced
Mode is selected. Actions that are not allowed include but
are not limited to:
1.1.5 Clocking
The ADC08D1520QML must be driven with an a.c. coupled,
differential clock signal. 2.4 THE CLOCK INPUTS describes
the use of the clock input pins. A differential LVDS output
clock is available for use in latching the ADC output data into
whatever device is used to receive the data.
Changing OUTV
The ADC08D1520QML offers input and output clocking op-
tions. These options include a choice of Dual Edge Sampling
(DES) or "interleaved mode" where the ADC08D1520QML
performs as a single device converting at twice the input clock
rate, a choice of which DCLK edge the output data transitions
on, and a choice of Single Data Rate (SDR) or Double Data
Rate (DDR) outputs.
Changing OutEdge or SDATA sense
Changing between SDR and DDR
Changing FSE or ECE
Changing DCLK_RST
Changing SCS
Raising PD high
Raising CAL high
The ADC08D1520QML also has the option to use a duty cycle
corrected clock receiver as part of the input clock circuit. This
feature is enabled by default and provides improved ADC
clocking especially in the Dual-Edge Sampling Mode
(DES). This circuitry allows the ADC to be clocked with a
signal source having a duty cycle ratio of 20%/80% (worst
case) for both the Non-DES and the Dual Edge Sampling
Modes.
•
Doing any of these actions can cause faulty calibration.
1.1.2 Acquiring the Input
Data is acquired at the falling edge of CLK+ (pin 18) and the
digital equivalent of that data is available at the digital outputs
13 input clock cycles later for the DI and DQ output buses and
14 input clock cycles later for the DId and DQd output buses.
There is an additional internal delay called tOD before the data
is available at the outputs. See the Timing Diagram. The AD-
C08D1520QML will convert as long as the input clock signal
is present. The fully differential comparator design and the
innovative design of the sample-and-hold amplifier, together
with self calibration, enables a very flat SINAD/ENOB re-
sponse beyond 1.5 GHz. The ADC08D1520QML output data
signaling is LVDS and the output format is offset binary.
1.1.5.1 Dual-Edge Sampling
The DES Mode allows one of the ADC08D1520QML's inputs
(I- or Q- Channel) to be sampled by both ADCs. One ADC
samples the input on the positive edge of the input clock and
the other ADC samples the same input on the other edge of
the input clock. A single input is thus sampled twice per input
clock cycle, resulting in an overall sample rate of twice the
input clock frequency, or 3 GSPS with a 1.5 GHz input clock.
1.1.3 Control Modes
In this mode, the outputs must be carefully interleaved to re-
construct the sampled signal. If the device is programmed into
the 1:2 Demultiplex Mode while in DES Mode, the data is ef-
fectively Demultiplexed 1:4. If the input clock is 1.5 GHz, the
effective sampling rate is doubled to 3 GSPS and each of the
4 output buses have a 750 MHz output rate. All data is avail-
able in parallel. To properly reconstruct the sampled wave-
form, the four bytes of parallel data that are output with each
clock are in the following sampling order from the earliest to
the latest and must be interleaved as such: DQd, DId, DQ, DI.
Table 1 indicates what the outputs represent for the various
sampling possibilities. If the device is programmed into the
Non-Demultiplex Mode, two bytes of parallel data are output
with each edge of the clock in the following sampling order,
from the earliest to the latest: DQ, DI. See Table 2.
Much of the user control can be accomplished with several
control pins that are provided. Examples include initiation of
the calibration cycle, Power Down Mode and full scale range
setting. However, the ADC08D1520QML also provides an
Extended Control mode whereby a serial interface is used to
access register-based control of several advanced features.
The Extended Control mode is not intended to be enabled and
disabled dynamically. Rather, the user is expected to employ
either the Non-Extended Control Mode or the Extended Con-
trol Mode at all times. When the device is in the Extended
Control Mode, pin-based control of several features is re-
placed with register-based control and those pin-based con-
trols are disabled. These pins are OutV (pin 3), OutEdge/DDR
(pin 4), FSR (pin 14) and DES (pin 127). See 1.2 NON-EX-
TENDED CONTROL/EXTENDED CONTROL for details on
the Extended Control Mode.
In the Non-Extended Control Mode of operation only the I-
channel input can be sampled in the DES Mode. In the
Extended Control Mode of operation, the user can select
which input is sampled.
1.1.4 The Analog Inputs
The ADC08D1520QML must be driven with a differential input
signal. Operation with a single-ended signal is not recom-
mended. It is important that the input signals are a.c. coupled
to the inputs.
The ADC08D1520QML also includes an automatic clock
phase background calibration feature which can be used in
DES Mode to automatically and continuously adjust the clock
phase of the I- and Q- channel. This feature removes the need
to adjust the clock phase setting manually and provides opti-
mal Dual-Edge Sampling ENOB performance.
Two full-scale range settings are provided with pin 14 (FSR).
A high on pin 14 causes an input full-scale range setting of a
higher VIN input level, while grounding pin 14 causes an input
full-scale range setting of a reduced VIN input level. The full-
scale range setting operates equally on both ADCs.
IMPORTANT NOTE: The background calibration feature in
DES Mode does not replace the requirement for calibration if
a large swing in ambient temperature is experienced by the
device.
In the Extended Control Mode, the Input Full-Scale Voltage
Adjust register allows the input full-scale range to be adjusted
as described in 1.4 REGISTER DESCRIPTION and 2.3 THE
ANALOG INPUT.
29
www.national.com
TABLE 1. Input Channel Samples Produced at Data Outputs in 1:2 Demultiplexed Mode**
Data Outputs Dual-Edge Sampling Mode (DES)
(Always sourced with
respect to fall of DCLK+)
Non DES Sampling Mode
I- Channel Selected
Q- Channel Selected *
I- Channel Input Sampled
with Fall of CLK 13 cycles
earlier.
I- Channel Input Sampled with
Fall of CLK 13 cycles earlier.
Q- Channel Input Sampled with
Fall of CLK 13 cycles earlier.
DI
DId
DQ
I- Channel Input Sampled
with Fall of CLK 14 cycles
earlier.
I- Channel Input Sampled with
Fall of CLK 14 cycles earlier.
Q- Channel Input Sampled with
Fall of CLK 14 cycles earlier.
I- Channel Input Sampled
with Rise of CLK 13.5 cycles
earlier.
Q- Channel Input Sampled with
Fall of CLK 13 cycles earlier.
Q- Channel Input Sampled with
Rise of CLK 13.5 cycles earlier.
I- Channel Input Sampled
with Rise of CLK 14.5 cycles
earlier.
Q- Channel Input Sampled with
Fall of CLK 14 cycles earlier.
Q- Channel Input Sampled with
Rise of CLK 14.5 cycles earlier.
DQd
* Note that, in DES + Non-DES Mode, only the I- Channel is sampled. In DES + Extended Control Mode, I- Channel or Q-
Channel can be sampled.
** Note that, in the Non-Demultiplexed Mode, the DId and DQd outputs are disabled and are high impedance.
TABLE 2. Input Channel Samples Produced at Data Outputs in 1:1 Demultiplexed Mode
Data Outputs
Non-DES Mode
DES Mode
(Sourced with respect to fall of DCLK+)
I- Channel Input Sampled with Fall of CLK I- Channel Input Sampled with Fall of CLK
DI
Dld
DQ
DQd
13 cycles earlier.
No output.
13 cycles earlier.
No output.
Q- Channel Input Sampled with Fall of
CLK 13 cycles earlier.
Q- Channel Input Sampled with Fall of
CLK 13.5 cycles earlier.
No output.
No output.
1.1.5.2 OutEdge and Demultiplex Control Setting
the data rate and data is sent to the outputs on both edges of
DCLK. DDR clocking is enabled in Non-Extended Control
Mode by tying pin 4 to VA/2.
To help ease data capture in the SDR Mode, the output data
may be caused to transition on either the positive or the neg-
ative edge of the output data clock (DCLK). In the Non-
Extended Control Mode, this is chosen with the OutEdge input
(pin 4). A high on the OutEdge input pin causes the output
data to transition on the rising edge of DCLK+, while ground-
ing this input causes the output to transition on the falling edge
of DCLK. See 2.5.3 Output Edge Synchronization. When in
the Extended Control Mode, the OutEdge is selected using
the OED bit in the Configuration Register. This bit has two
functions. In the single data rate (SDR) Mode, the bit functions
as OutEdge and selects the DCLK edge with which the data
transitions. In the Double Data Rate (DDR) Mode, this bit se-
lects whether the device is in Non-Demultiplex or 1:2 Demul-
tiplex Mode. In the DDR case, the DCLK has a 0° phase
relationship with the output data independent of the demulti-
plexer selection.
1.1.5.4 Clocking Summary
The chip may be in one of four modes, depending on the Dual-
Edge Sampling (DES) selection and the demultiplex selec-
tion. For the DES selection, there are two possibilities: Non-
DES Mode and DES Mode. In Non-DES Mode, each of the
channels (I-channel and Q-channel) functions independently,
i.e. the chip is a dual 1.5 GSPS A/D converter. In DES Mode,
the I- and Q-channels are interleaved and function together
as one 3.0 GSPS A/D converter. For the demultiplex selec-
tion, there are also two possibilities: Demux Mode and Non-
Demux Mode. The I-channel has two 8-bit output busses
associated with it: DI and DId. The Q-channel also has two 8-
bit output busses associated with it: DQ and DQd. In Demux
Mode, the channel is demultiplexed by 1:2. In Non-Demux
Mode, the channel is not demultiplexed. Note that Non-De-
mux Mode is also sometimes referred to as 1:1 Demux Mode.
For example, if the I-channel was in Non-Demux Mode, the
corresponding digital output data would be available on only
the DI bus. If the I-channel was in Demux Mode, the corre-
sponding digital output data would be available on both the
DI and DId busses, but at half the rate of Non-Demux Mode.
For 1:2 Demux DDR 0 deg Mode, there are five, as opposed
to four cycles of CLK delay from the deassertion of
DCLK_RST to the Synchronizing Edge. See 1.5 MULTIPLE
ADC SYNCHRONIZATION
1.1.5.3 Double Data Rate
A choice of single data rate (SDR) or double data rate (DDR)
output is offered. With single data rate the output clock
(DCLK) frequency is the same as the data rate of the two out-
put buses. With double data rate the DCLK frequency is half
Given that there are two DES Mode selections (DES Mode
and Non-DES Mode) and two demultiplex selections (Demux
Mode and Non-Demux Mode), this yields a total of four pos-
www.national.com
30
sible modes: (1) Non-Demux Mode, (2) Non-Demux DES
Mode, (3) 1:2 Demux Non-DES Mode, and (4) 1:4 Demux
DES Mode. The following is a brief explanation of the terms
and modes:
power consumption. If the LVDS lines are long and/or the
system in which the ADC08D1520QML is used is noisy, it may
be necessary to tie the OutV pin high.
The LVDS data output have a typical common mode voltage
of 800 mV when the VBG pin is left floating. This common
mode voltage can be increased to 1.1V by tying the VBG pin
to VA if a higher common mode is required.
1. Non-Demux Mode: This mode is when the chip is in Non-
Demux Mode and Non-DES Mode, but it is shortened to
simply "Non-Demux Mode." The I- and Q- channels
function independently of one another. The digital output
data is available for the I- channel on DI, and for the Q-
channel on DQ.
IMPORTANT NOTE: Tying the VBG pin to VA will also in-
crease the differential LVDS output voltage by up to 40mV.
1.1.7 Power Down
2. Non-Demux DES Mode: This mode is when the chip is
in Non-Demux Mode and DES Mode. The I- and Q-
channels are interleaved and function together as one
channel. The digital output data is available on the DI and
DQ busses because although the chip is in Non-Demux
Mode, both I- and Q- channels are functioning and
passing data.
The ADC08D1520QML is in the active state when the Power
Down pin (PD) is low. When the PD pin is high, the device is
in the Power Down Mode. In this Power Down Mode the data
output pins (positive and negative) are put into a high
impedance state and the devices power consumption is re-
duced to a minimal level. The DCLK+/- and OR +/- are not tri-
stated, they are weakly pulled down to ground internally.
Therefore when both I- Channel and Q- Channel are powered
down the DCLK +/- and OR +/- should not be terminated to a
DC voltage.
3. 1:2 Demux Non-DES Mode: This mode is when the chip
is in Demux Mode and Non-DES Mode. The I- and Q-
channels function independently of one another. The
digital output data is available for the I- channel on DI and
DId, and for the Q- channel on DQ and DQd. This is
because each channel (I- channel and Q- channel) is
providing digital data in a demultiplexed manner.
A high on the PDQ pin will power down the Q- Channel and
leave the I- channel active. There is no provision to power
down the I- Channel independently of the Q- Channel. Upon
return to normal operation, the pipeline will contain meaning-
less information.
4. 1:4 Demux DES Mode: This mode is when the chip is in
Demux Mode and DES Mode. The I- and Q- channels
are interleaved and function together as one channel.
The digital output data is available on the DI, DId, DQ and
DQd busses because although the chip is in Demux
Mode, both I- and Q- channels are functioning and
passing data. To avoid confusion, this mode is labeled
1:4 because the analog input signal is provided on one
channel and the digital output data is provided on four
busses.
If the PD input is brought high while a calibration is running,
the device will not go into power down until the calibration
sequence is complete. However, if power is applied and PD
is simultaneously ramped, the device will not calibrate until
the PD input goes low. If a calibration is requested while the
device is powered down, the calibration request will be com-
pletely ignored. Calibration will function with the Q- Channel
powered down, but that channel will not be calibrated if PDQ
is high. If the Q- Channel is subsequently to be used, it is
necessary to perform a calibration after PDQ is brought low.
The choice of Dual Data Rate (DDR) and Single Data Rate
(SDR) will only affect the speed of the output Data Clock
(DCLK). Once the DES Modes and Demux Modes have been
chosen, the data output rate is also fixed. In the case of SDR,
the DCLK runs at the same rate as the output data; output
data may transition with either the rising or falling edge of
DCLK. In the case of DDR, the DCLK runs at half the rate of
the output data; the output data transitions on both rising and
falling edges of the DCLK.
1.2 NON-EXTENDED CONTROL/EXTENDED CONTROL
The ADC08D1520QML may be operated in one of two
modes. In the simpler Non-Extended Control Mode, the user
affects available configuration and control of the device
through several control pins. The "Extended Control Mode"
provides additional configuration and control options through
a serial interface and a set of 9 registers. Extended Control
Mode is selected by setting pin 41 to logic low. The choice of
control modes is required to be a fixed selection and is not
intended to be switched dynamically while the device is op-
erational.
1.1.6 The LVDS Outputs
The data outputs, the Out Of Range (OR) and DCLK, are
LVDS. Output current sources provide 3 mA of output current
to a differential 100 Ohm load when the OutV input (pin 14) is
high or 2.2 mA when the OutV input is low. For short LVDS
lines and low noise systems, satisfactory performance may
be realized with the OutV input low, which results in lower
Table 3 shows how several of the device features are affected
by the control mode chosen.
31
www.national.com
TABLE 3. Features and Modes
Non-Extended Control Mode
Feature
Extended Control Mode
Selected with bit 10 nDE in the Configuration Register
(Addr-1h; bit-10)
SDR or DDR Clocking Selected with pin 4
Selected with DCP in the Configuration
Register (Addr-1h; bit-11)
DDR Clock Phase
Not Selectable (0° Phase Only)
SDR Data transitions SDR Data transitions with rising
with rising or falling
DCLK edge
edge of DCLK+ when pin 4 is high Selected with OED in the Configuration Register (Addr-1h; bit-8)
and on falling edge when low.
Normal differential data and DCLK
amplitude selected when pin 3 is
LVDS output level
Selected with OV in the Configuration Register (Addr-1h; bit-9)
high and reduced amplitude
selected when low.
Normal input full-scale range
Up to 512 step adjustments over a nominal range specified in 1.4
selected when pin 14 is high and
REGISTER DESCRIPTION. Separate range selected for I-
reduced range when low.
Full-Scale Range
Input Offset Adjust
Channel and Q- Channels. Selected using Full Range
Selected range applies to both
Registers (Addr-3h and Bh; bit-7 thru 15)
channels.
512 steps of adjustment using the input Offset register specified
Not possible
in 1.4 REGISTER DESCRIPTION for each channel using Input
Offset registers (Addr-2h and Ah; bit-7 thru 15)
Dual Edge Sampling
Selection
Enabled by programming DEN in the Extended Configuration
Register (Addr-9h; bit-13 )
Enabled with pin 127 set to VA/2
Only I-Channel Input can be used
Not possible
Dual Edge Sampling
Input Channel
Selection
Either I- Channel or Q- Channel input may be sampled by both
ADCs.
A test pattern can be made present at the data outputs by setting
TPO to 1b in Extented Configuration Register (Addr-9h; bit-15)
Test Pattern
The DCLK outputs will continuously be present when RTD is set
to 1b in Extented Configuration Register (Addr-9h; bit-14)
Resistor Trim Disable Not possible
If the device is set in DDR, the output can be programmed to be
non-demultiplex. When OED in Configuration Register is set 1b
(Addr-1h; 8-bit), this selects non-demultiplex. If OED is set 0b,
this selects 1:2 demultiplex.
Selectable Output
Not possible
Demultiplexer
The OR outputs can be programmed to become a second DCLK
output when nSD is set 0b in Configuration Register
(Addr-1h; bit-13).
Second DCLK Output Not possible
The sampling clock phase can be manually adjusted through the
Coarse and Intermediate Register (Addr-Fh; bit-14 to 7) and Fine
register (Addr-Dh; bit-15 to 8)
Sampling Clock Phase
Not possible
Adjust
When the device is powered up in the Extended Control
Mode, the Registers are loaded with invalid data and the
Registers come up on an unknown state. Before initiating a
calibration the registers must be written to and programmed
into a known state. If the device is powered up in the Non-
Extended Control Mode and the user switches to the Extend-
ed Control Mode after the part has stabilized, the registers will
load with the register default states described in Table 4.
www.national.com
32
TABLE 4. Extended Control Mode Operation
(Pin 41 Logic Low)
Feature
Extended Control Mode Default State
DDR Clocking
SDR or DDR Clocking
DDR Clock Phase
Data changes with DCLK edge (0° phase)
Normal amplitude
LVDS Output Amplitude
(VOD
)
Full-Scale Range
Input Offset Adjust
700 mV nominal for both channels
No adjustment for either channel
Not enabled
Dual Edge Sampling (DES)
Test Pattern
Not present at output
Resistor Trim Disable
Selectable Output Demultiplexer
Second DCLK Output
Sampling Clock Phase Adjust
Trim enabled, DCLK not continuously present at output
1:2 demultiplex
Not present, pin 79 and 80 function as OR+ and OR-.
No adjustment for fine, intermediate or coarse
1.3 THE SERIAL INTERFACE
TABLE 5. Register Addresses
4-Bit Address
The 3-pin serial interface is enabled only when the device is
in the Extended Control mode. The pins of this interface are
Serial Clock (SCLK), Serial Data (SDATA) and Serial Inter-
face Chip Select (SCS). Nine write only registers are acces-
sible through this serial interface.
Loading Sequence:
A3 loaded after H0, A0 loaded last
A3
0
A2
0
A1
0
A0 Hex
Register Addressed
Calibration
SCS: This signal should be asserted low while accessing a
register through the serial interface. Setup and hold times with
respect to the SCLK must be observed.
0
1
0
0h
1h
2h
0
0
0
Configuration
I- Ch Offset
0
0
1
SCLK: Serial data input is accepted at the rising edge of this
signal.
I- Ch Full-Scale
Voltage Adjust
0
0
1
1
3h
SDATA: Each register access requires a specific 32-bit pat-
tern at this input. This pattern consists of a header, register
address and register value. The data is shifted in MSB first.
Setup and hold times with respect to the SCLK must be ob-
served. See the Timing Diagram.
0
0
0
0
1
1
1
1
1
0
0
0
1
1
0
0
1
0
1
0
4h
5h
6h
7h
8h
Reserved
Reserved
Reserved
Reserved
Reserved
Each Register access consists of 32 bits, as shown in Figure
6 of the Timing Diagrams. The fixed header pattern is 0000
0000 0001 (eleven zeros followed by a 1). The loading se-
quence is such that a "0" is loaded first. These 12 bits form
the header. The next 4 bits are the address of the register that
is to be written to and the last 16 bits are the data written to
the addressed register. The addresses of the various regis-
ters are indicated in Table 5.
Extended
Configuration
1
1
1
0
0
0
0
1
1
1
0
1
9h
Ah
Bh
Q- Ch Offset
Q- Ch Full-Scale
Voltage Adjust
Refer to the Register Description (1.4 REGISTER DESCRIP-
TION) for information on the data to be written to the registers.
1
1
1
1
0
0
0
1
Ch
Dh
Reserved
Reserved
Subsequent register accesses may be performed immediate-
ly, starting with the 33rd SCLK. This means that the SCS input
does not have to be de-asserted and asserted again between
register addresses. It is possible, although not recommended,
to keep the SCS input permanently enabled (at a logic low)
when using extended control.
Sampling Clock Phase
Fine Adjust
1
1
1
0
Eh
Sample Clock Phase
Intermediate and
Coarse Adjust
1
1
1
1
Fh
IMPORTANT NOTE: Do not write to the Serial Interface when
calibrating the ADC. Doing so will impair the performance of
the device until it is re-calibrated correctly. Programming the
serial registers will also reduce dynamic performance of the
ADC for the duration of the register access time.
33
www.national.com
1.4 REGISTER DESCRIPTION
Bit 10
nDE: DDR Enable. When this bit is set to 0b,
data bus clocking follows the DDR (Double
Data Rate) Mode whereby a data word is
output with each rising and falling edge of
DCLK. When this bit is set to a 1b, data bus
clocking follows the SDR (single data rate)
Mode whereby each data word is output with
either the rising or falling edge of DCLK , as
determined by the OutEdge bit.
Nine write-only registers provide several control and config-
uration options in the Extended Control Mode. These regis-
ters have no effect when the device is in the Non-Extended
Control Mode. Each register description below also shows the
Register Default State.
Calibration Register
Addr: 0h (0000b)
Write only (0x7FFF)
D15 D14 D13 D12 D11 D10
D9
1
D8
1
Default State: 0b
CAL
1
1
1
1
1
Bit 9
OV: Output Voltage. This bit determines the
LVDS outputs' voltage amplitude and has the
same function as the OutV pin that is used in
the Non-Extended Control Mode. When this bit
is set to 1b, the standard output amplitude of
780 mVP-P is used. When this bit is set to 0b,
the reduced output amplitude of 590 mVP-P is
used.
D7
1
D6
1
D5
1
D4
1
D3
1
D2
1
D1
1
D0
1
Bit 15
CAL: Calibration Enable. When this bit is set
1b, a command calibration cycle is initiated.
This function is exactly the same as issuing
a calibration using the CAL pin. See section
2.5.2.1, Initiating Calibration for details for
usage.
Default State: 1b
Bit 8
OED: Output Edge and Demultiplex Control.
This bit has two functions. When the device is
in SDR Mode, this bit selects the DCLK edge
with which the data words transition in the
SDR Mode and has the same effect as the
OutEdge pin in the Non-Extended Control
Mode. When this bit is set to 1b, the data
outputs change with the rising edge of DCLK
+. When this bit is set to 0b, the data output
changes with the falling edge of DCLK+. When
the device is in DDR Mode, this bit selects the
Non-Demultiplexed Mode when set to 1b.
When the bit set to 0b, the device is
programmed into the 1:2 Demultiplexed Mode.
The 1:2 Demultiplexed Mode is the default
mode. In DDR Mode, DCLK has a 0° phase
relationship with the data.
Default State: 0b
Bits 14:0 Must be set to 1b
Configuration Register
Addr: 1h (0001b) Write only (0xB2FF)
D15 D14 D13 D12 D11 D10 D9 D8
nSD DCS DCP nDE OV OED
1
0
D7
1
D6
1
D5
1
D4
1
D3
1
D2
1
D1
1
D0
1
Bit 15
Bit 14
Bit 13
Must be set to 1b
Must be set to 0b
nSD: Second DCLK Output. When this bit is
1b, the device only has one DCLK output and
one OR output. When this output is 0b, the
device has two identical DCLK outputs and no
OR output.
Default State: 0b
Bits 7:0
Must be set to 1b
Default State: 1b
I-Channel Offset
Bit 12
Bit 11
DCS: Duty Cycle Stabilizer. When this bit is set
to 1b, a duty cycle stabilization circuit is
applied to the clock input. When this bit is set
to 0b the stabilization circuit is disabled.
Default State: 1b
Addr: 2h (0010b)
Write only (0x007F)
D15 D14 D13 D12 D11 D10
D9
D8
(MSB)
Offset Value
(LSB)
DCP: DDR Clock Phase. This bit only has an
effect in the DDR Mode. When this bit is set to
0b, the DCLK edges are time-aligned with the
data bus edges ("0° Phase"). When this bit is
set to 1b, the DCLK edges are placed in the
middle of the data bit-cells ("90° Phase"),
using the one-half speed DCLK shown in
Figure 4 as the phase reference.
D7
D6
1
D5
1
D4
1
D3
1
D2
1
D1
1
D0
1
Sign
Bits 15:8 Offset Value. The input offset of the I-Channel
ADC is adjusted linearly and monotonically by
the value in this field. 00h provides a nominal
zero offset, while FFh provides a nominal 45
mV of offset. Thus, each code step provides
0.176 mV of offset.
Default State: 0b
Default State: 0000 0000 b
Bit 7
Sign bit. 0b gives positive offset, 1b gives
negative offset.
Default State: 0b
Bit 6:0
Must be set to 1b
www.national.com
34
I-Channel Full-Scale Voltage Adjust
Addr: 3h (0011b) Write only (0x807F)
Bit 13
DES: DES Enable. Setting this bit to 1b
enables the Dual Edge Sampling Mode. In
this mode the ADCs in this device are used
to sample and convert the same analog input
in a time-interleaved manner, accomplishing
a sample rate of twice the input clock rate.
When this bit is set to 0b, the device operates
in the Non-DES Mode.
D15
D14 D13 D12 D11 D10
Adjust Value
D9
D8
(MSB)
D7
D6
1
D5
1
D4
1
D3
1
D2
1
D1
1
D0
1
(LSB)
Default State: 0b
Bit 15:7
Full Scale Voltage Adjust Value. The input full-
scale voltage or gain of the I-Channel ADC is
adjusted linearly and monotonically with a 9 bit
data value. The adjustment range is ±20% of
the nominal 700 mVP-P differential value.
Bit 12
IS: Input Select. When this bit is set to 0b the
I- Channel input is operated upon by both
ADCs. When this bit is set to 1b the Q-
Channel input is operated on by both ADCs.
Default State: 0b
Must be set to 0b
0000 0000 0
560mVP-P
700mVP-P
Bit 11
Bit 10
1000 0000 0
Default Value
1111 1111 1
DLF: DES Low Frequency. When this bit is
set 1b, the dynamic performance of the
device is improved when the input clock is
less than 900 MHz.
840mVP-P
For best performance, it is recommended that
the value in this field be limited to the range of
0110 0000 0b to 1110 0000 0b. i.e., limit the
amount of adjustment to ±15%. The remaining
±5% headroom allows for the ADC's own full
scale variation. A gain adjustment does not
require ADC re-calibration.
Default State: 0b
Must be set to 1b
Bits 9:0
Q- Channel Offset
Addr: Ah (1010b)
Write only (0x007F)
D15 D14 D13 D12 D11 D10
D9
D8
Default State: 1000 0000 0b (no adjustment)
(MSB)
Offset Value
(LSB)
Bits 6:0 Must be set to 1b
Extended Configuration Register
Addr: 9h (1001b) Write only (0x03FF)
D15 D14 D13 D12 D11 D10
D7
D6
1
D5
1
D4
1
D3
1
D2
1
D1
1
D0
1
Sign
Bit 15:8
Offset Value. The input offset of the Q-
Channel ADC is adjusted linearly and
monotonically by the value in this field. 00h
provides a nominal zero offset, while FFh
provides a nominal 45 mV of offset. Thus,
each code step provides about 0.176 mV of
offset.
D9
1
D8
1
TPO RTD DEN
IS
0
DLF
D7
1
D6
1
D5
1
D4
1
D3
1
D2
1
D1
1
D0
1
Bit 15
Bit 14
TPO: Test Pattern Output. When this bit is set
1b, the ADC is disengaged and a test pattern
generator is connected to the outputs
including OR. This test pattern will work with
the device in the SDR, DDR and the Non-
Demultiplex output modes.
Default State: 0000 0000 b
Bit 7
Sign bit. 0b gives positive offset, 1b gives
negative offset.
Default State: 0b
Bit 6:0
Must be set to 1b
Default State: 0b
RTD: Resistor Trim Disable. When this bit is
set to 1b, the input termination resistor is not
trimmed during the calibration cycle and the
DCLK output remains enabled. Note that the
ADC is calibrated regardless of this setting.
Default State: 0b
35
www.national.com
Q- Channel Full-Scale Voltage Adjust
Addr: Bh (1011b) Write only (0x807F)
Bit 15
Polarity Select. When this bit is selected, the
polarity of the ADC sampling clock is
inverted.
D15
D14 D13 D12 D11 D10
Adjust Value
D9
D8
Default State: 0b
(MSB)
Bits 14:10 Coarse Phase Adjust. Each code value in
this field delays the sample clock by
approximately 65 ps. A value of 00000b in
this field causes zero adjustment.
D7
D6
1
D5
1
D4
1
D3
1
D2
1
D1
1
D0
1
(LSB)
Default State: 00000b
Bit 15:7
Full Scale Voltage Adjust Value. The input full-
scale voltage or gain of the I- Channel ADC is
adjusted linearly and monotonically with a 9 bit
data value. The adjustment range is ±20% of
the nominal 700 mVP-P differential value.
Bits 9:7
Intermediate Phase Adjust. Each code value
in this field delays the sample clock by
approximately 11 ps. A value of 000b in this
field causes zero adjustment. Maximum
combined adjustment using Coarse Phase
Adjust and Intermediate Phase adjust is
approximately 2.1ns.
0000 0000 0
1000 0000 0
1111 1111 1
560 mVP-P
700 mVP-P
840 mVP-P
Default State: 000b
Bits 6:0
Must be set to 1b
For best performance, it is recommended that
the value in this field be limited to the range of
0110 0000 0b to 1110 0000 0b. i.e., limit the
amount of adjustment to ±15%. The remaining
±5% headroom allows for the ADC's own full
scale variation. A gain adjustment does not
require ADC re-calibration.
Note Regarding Extended Mode Offset Correction
When using the I- Channel or Q- Channel Offset Adjust reg-
isters, the following information should be noted.
For offset values of +0000 0000 and -0000 0000, the actual
offset is not the same. By changing only the sign bit in this
case, an offset step in the digital output code of about 1/10th
of an LSB is experienced. This is shown more clearly in the
Figure below.
Default State: 1000 0000 0b (no adjustment)
Must be set to 1b
Note Regarding Clock Phase Adjust
Bits 6:0
This is a feature intended to help the system designer remove
small imbalances in clock distribution traces at the board level
when multiple ADCs are used. Please note, however, that
enabling this feature will reduce the dynamic performance
(ENOB, SNR SFDR) some finite amount. The amount of
degradation increases with the amount of adjustment applied.
The user is strongly advised to (a) use the minimal amount of
adjustment: and (b) verify the net benefit of this feature in his
system before relying on it.
Sample Clock Phase Fine Adjust
Addr: Eh (1110b)
Write only (0x00FF)
D15 D14 D13 D12 D11 D10
D9
D8
(MSB)
Fine Phase Adjust
(LSB)
D7
1
D6
1
D5
1
D4
1
D3
1
D2
1
D1
1
D0
1
Bits 15:8 Fine Phase Adjust. The phase of the ADC
sampling clock is adjusted linearly and
monotonically by the value in this field. 00h
provides a nominal zero phase adjustment,
while FFh provides a nominal 50 ps of delay.
Thus, each code step provides about 0.2 ps
of delay.
Default State: 0000 0000b
Bits 7:0
Must be set to 1b
Sample Clock Phase Intermediate/Coarse Adjust
Addr: Fh (1111b) Write only (0x007F)
D15
POL
D14 D13 D12 D11 D10
(MSB) Coarse Phase Adjust
D9
D8
IPA
30024730
D7
D6
1
D5
1
D4
1
D3
1
D2
1
D1
1
D0
1
FIGURE 11. Extended Mode Offset Behavior
(LSB)
www.national.com
36
1.5 MULTIPLE ADC SYNCHRONIZATION
8-bit word, alternating between 1's and 0's as described in the
Table 6.
The ADC08D1520QML has the capability to precisely reset
its sampling clock input to DCLK output relationship as de-
termined by the user-supplied DCLK_RST pulse. This allows
multiple ADCs in a system to have their DCLK (and data) out-
puts transition at the same time with respect to the shared
CLK input that they all the ADCs use for sampling.
TABLE 6. Test Pattern by Output Port
in 1:2 Demultiplex Mode
Time
T0
Qd
01h
FEh
01h
FEh
01h
01h
FEh
01h
FEh
01h
01h
...
Id
Q
I
OR
0
Comments
02h
FDh
02h
FDh
02h
02h
FDh
02h
FDh
02h
02h
...
03h 04h
FCh FBh
03h 04h
FCh FBh
03h 04h
03h 04h
FCh FBh
03h 04h
FCh FBh
03h 04h
03h 04h
The DCLK_RST signal must observe some timing require-
ments that are shown in Figure 7, Figure 8 and Figure 9 of the
Timing Diagrams. The DCLK_RST pulse must be of a mini-
mum width and its deassertion edge must observe setup and
hold times with respect to the CLK input rising edge. These
timing specifications are listed as tRH, tRS, and tRPW in the
Converter Electrical Characteristics.
T1
1
Pattern
Sequence
n
T2
0
T3
1
T4
0
T5
0
T6
1
Pattern
Sequence
n+1
The DCLK_RST signal can be asserted asynchronous to the
input clock. If DCLK_RST is asserted, the DCLK output is held
in a designated state. The state in which DCLK is held during
the reset period is determined by the mode of operation (SDR/
DDR) and the setting of the Output Edge configuration pin or
bit. (Refer to Figure 7, Figure 8 and Figure 9 for the DCLK
reset state conditions). Therefore, depending upon when the
DCLK_RST signal is asserted, there may be a narrow pulse
on the DCLK line during this reset event. When the
DCLK_RST signal is de-asserted in synchronization with the
CLK rising edge, the 4th or 5th CLK falling edge synchronizes
the DCLK output with those of other ADC08D1520QMLs in
the system. The DCLK output is enabled again after a con-
stant delay (relative to the input clock frequency) which is
equal to the CLK input to DCLK output delay (tSD). The device
always exhibits this delay characteristic in normal operation.
T7
0
T8
1
T9
0
T10
T11
0
Pattern
Sequence n+2
...
...
...
With the part programmed into the Non-Demultiplex Mode,
the test pattern’s order will be as described in Table 7.
TABLE 7. Test Pattern by Output Port in
Non-Demultiplex Mode
Time
T0
Q
I
OR
0
Comments
01h
FEh
01h
01h
FEh
FEh
01h
01h
FEh
01h
01h
FEh
01h
01h
FEh
...
02h
FDh
02h
02h
FDh
FDh
02h
02h
FDh
02h
02h
FDh
02h
02h
FDh
...
T1
1
As shown in Figure 7, Figure 8 and Figure 9of the Timing Di-
agrams, there is a delay from the deassertion of DCLK_RST
to the reappearance of DCLK, which is equal to several CLK
cycles of delay plus tSD. Note that the deassertion of
DCLK_RST is not latched in until the next falling edge of CLK.
For 1:2 Demux DDR 0 deg Mode, there are five CLK cycles
of delay; for all other modes, there are four CLK cycles of
delay.
T2
0
T3
0
Pattern
Sequence
n
T4
1
T5
1
T6
0
T7
0
If the device is not programmed to allow DCLK to run contin-
uously, DCLK will become inactive during a calibration cycle.
Therefore, it is strongly recommended that DCLK only be
used as a data capture clock and not as a system clock.
T8
1
T9
0
T10
T11
T12
T13
T14
T15
0
The DCLK_RST pin should NOT be brought high while the
calibration process is running (while CalRun is high). Doing
so could cause a digital glitch in the digital circuitry, resulting
in corruption and invalidation of the calibration. (See Applica-
tion Information Section 2.4.3)
1
Pattern
Sequence
n+1
0
0
1
...
1.6 ADC TEST PATTERN
To aid in system debug, the ADC08D1520QML has the ca-
pability of providing a test pattern at the four output ports
completely independent of the input signal. The ADC is dis-
engaged and a test pattern generator is connected to the
outputs including OR. The test pattern output is the same in
DES Mode and Non-DES Mode. Each port is given a unique
To ensure that the test pattern starts synchronously in each
port, set DCLK_RST while writing the Test Pattern Output bit
in the Extended Configuration Register. The pattern appears
at the data output ports when DCLK_RST is cleared low. The
test pattern will work at speed and will work with the device in
the SDR, DDR and the Non-Demultiplex output modes.
37
www.national.com
FSR pin grounded, the millivolt values in Table 8 are reduced
to 75% of the values indicated. In the Extended Control Mode,
these values will be determined by the full scale range and
offset settings in the Control Registers.
2.0 Applications Information
2.1 APPLICATIONS IN RADIATION ENVIRONMENTS
Applying the ADC08D1520QML in a radiation environment
should be done with careful consideration to that environ-
ment. The QMLV version of this part has been rated to tolerate
a high total dose of ionizing radiation by test method 1019 of
MIL-STD-883. The part is also immune to SEE (Single Event
Effects) hard errors such as Single Event Latch-up and Func-
tional Interrupts. However, there are still some recommenda-
tions and cautions.
TABLE 8. Differential Input To Output Relationship
(Non-Extended Control Mode, FSR High)
VIN+
VIN−
Output Code
0000 0000
0100 0000
VCM − 225 mV
VCM − 113 mV
VCM + 225 mV
VCM + 113 mV
0111 1111 /
1000 0000
Floating pins. There are four tri-level pins which activate the
following modes when left floating: FSR/DCLK_RST-, Out-
Edge/DDR/SDATA, DRST_SEL and DES/SCS. If modes re-
quiring a floating pin are needed to be used, then it is strongly
recommended that the floating method of establishing Va/2
on these pins not be employed. Due to the potential of in-
creased leakage of the input protection diodes after large
ionizing doses, the midpoint voltage (Va/2 or 0.95V) should
be voltage forced or formed with a resistor divider from the
analog supply to ground with two 2K ohm resistors. The tol-
erance for this mid point voltage is 650mV ≥ VA/2 ≤ 1.2V. The
internal voltage divider resistors provide too little current to
set the midpoint voltage reliably in radiation environments.
VCM
VCM
VCM + 109 mV
VCM −109 mV
1100 0000
1111 1111
VCM + 217.5 mV VCM − 217.5 mV
The buffered analog inputs simplify the task of driving these
inputs and the RC pole that is generally used at sampling ADC
inputs is not required. If it is desired to use an amplifier circuit
before the ADC, use care in choosing an amplifier with ade-
quate noise and distortion performance and adequate gain at
the frequencies used for the application.
IMPORTANT NOTE: An Analog input channel that is not used
(e.g. in DES Mode) should be left floating when the inputs are
a.c. coupled. Do not connect an unused analog input to
ground.
2.2 THE REFERENCE VOLTAGE
The voltage reference for the ADC08D1520QML is derived
from a 1.254V bandgap reference, a buffered version of which
is made available at pin 31, VBG, for user convenience. This
output has an output current capability of ±100 μA and should
be buffered if more current is required.
The internal bandgap-derived reference voltage has a nomi-
nal value VIN, as determined by the FSR pin and described in
1.1.4 The Analog Inputs.
There is no provision for the use of an external reference volt-
age, but the full-scale input voltage can be adjusted through
a Full Scale Register in the Extended Control Mode, as ex-
plained in 1.2 NON-EXTENDED CONTROL/EXTENDED
CONTROL.
30024744
FIGURE 12. Differential Input Drive
Differential input signals up to the chosen full-scale level will
be digitized to 8 bits. Signal excursions beyond the full-scale
range will be clipped at the output. These large signal excur-
sions will also activate the OR output for the time that the
signal is out of range. See 2.3.2 Out Of Range (OR) Indica-
tion.
2.3.1 Handling Single-Ended Input Signals
There is no provision for the ADC08D1520QML to adequately
process single-ended input signals. The best way to handle
single-ended signals is to convert them to differential signals
before presenting them to the ADC. The easiest way to ac-
complish single-ended to differential signal conversion is with
an appropriate balun-connected transformer, as shown in
Figure 13.
One extra feature of the VBG pin is that it can be used to raise
the common mode voltage level of the LVDS outputs. The
output offset voltage (VOS) is typically 800 mV when the VBG
pin is used as an output or left unconnected. To raise the
LVDS offset voltage to a typical value of 1100 mV the VBG pin
can be connected directly to the supply rails.
2.3.1.1. a.c. Coupled Input
The easiest way to accomplish single-ended a.c. Input to dif-
ferential a.c. signal is with an appropriate balun, as shown in
Figure 13.
2.3 THE ANALOG INPUT
The analog input is a differential one to which the signal
source must be a.c. coupled as shown in Figure 12. In the
Non-Extended Control Mode, the full-scale input range is se-
lected with the FSR pin as specified in the Converter Electrical
Characteristics. In the Extended Control Mode, the full-scale
input range is selected by programming the Full-Scale Volt-
age Adjust register through the Serial Interface. For best
performance, when adjusting the input full-scale range in the
Extended Control, refer to 1.4 REGISTER DESCRIPTION for
guidelines on limiting the amount of adjustment.
Table 8 gives the input to output relationship with the FSR pin
high when the normal (Non-Extended) Mode is used. With the
www.national.com
38
tested and its performance is guaranteed with a differential
1.5 GHz clock, it typically will function well with input clock
frequencies indicated in the Converter Electrical Character-
istics. The clock inputs are internally terminated and biased.
The input clock signal must be capacitive coupled to the clock
pins as indicated in Figure 14.
Operation up to the sample rates indicated in the Converter
Electrical Characteristics is typically possible if the maximum
ambient temperatures indicated are not exceeded. Operating
at higher sample rates than indicated for the given ambient
temperature may result in reduced device reliability and prod-
uct lifetime. This is because of the higher power consumption
and die temperatures at high sample rates. Important also for
reliability is proper thermal management. See 2.7.2 Thermal
Management.
30024743
FIGURE 13. Single-Ended to Differential Signal
Conversion using a Balun
Figure 13 is a generic depiction of a single-ended to differen-
tial signal conversion using a balun. The circuitry specific to
the balun will depend upon the type of balun selected and the
overall board layout. It is recommended that the system de-
signer contact the manufacturer of the balun they have se-
lected to aid in designing the best performing single-ended to
differential conversion circuit using that particular balun.
When selecting a balun, it is important to understand the input
architecture of the ADC. There are specific balun parameters
of which the system designer should be mindful. A designer
should match the impedance of the analog source to the
ADC08D1520QML’s on-chip 100Ω differential input termina-
tion resistor. The range of this input termination resistor is
described in the Converter Electrical Characteristics as the
specification RIN.
30024747
Also, the phase and amplitude balance are important. The
lowest possible phase and amplitude imbalance is desired
when selecting a balun. The phase imbalance should be no
more than ±2.5° and the amplitude imbalance should be lim-
ited to less than 1dB at the desired input frequency range.
FIGURE 14. Differential (LVDS) Input Clock Connection
The differential input clock line pair should have a character-
istic impedance of 100Ω and (when using a balun), be termi-
nated at the clock source in that (100 Ω) characteristic
impedance. The input clock line should be as short and as
direct as possible. The ADC08D1520QML clock input is in-
ternally terminated with an untrimmed 100Ω resistor.
Insufficient input clock levels will result in poor dynamic per-
formance. Excessively high input clock levels could cause a
change in the analog input offset voltage. To avoid these
problems, keep the input clock level within the range specified
in the Converter Electrical Characteristics.
Finally, when selecting a balun, the VSWR (Voltage Standing
Wave Ratio), bandwidth and insertion loss of the balun should
also be considered. The VSWR aids in determining the overall
transmission line termination capability of the balun when in-
terfacing to the ADC input. The insertion loss should be
considered so that the signal at the balun output is within the
specified input range of the ADC as described in the Con-
verter Electrical Characteristics as the specification VIN.
The low and high times of the input clock signal can affect the
performance of any A/D Converter. The ADC08D1520QML
features a duty cycle clock correction circuit which can main-
tain performance over temperature even in DES Mode. The
ADC will meet its performance specification if the input
clock high and low times are maintained within the range
(20/80% ratio).
High speed, high performance ADCs such as the AD-
C08D1520QML require a very stable input clock signal with
minimum phase noise or jitter. ADC jitter requirements are
defined by the ADC resolution (number of bits), maximum
ADC input frequency and the input signal amplitude relative
to the ADC input full scale range. The maximum jitter (the sum
of the jitter from all sources) allowed to prevent a jitter-induced
reduction in SNR is found to be
2.3.2 Out Of Range (OR) Indication
When the conversion result is clipped the Out of Range output
is activated such that OR+ goes high and OR- goes low. This
output is active as long as accurate data on either or both of
the buses would be outside the range of 00h to FFh. Note that
when the device is programmed to provide a second DCLK
output, the OR signals become DCLK2. Refer to 1.4 REGIS-
TER DESCRIPTION.
2.3.3 Full-Scale Input Range
As with all A/D Converters, the input range is determined by
the value of the ADC's reference voltage. The reference volt-
age of the ADC08D1520QML is derived from an internal
band-gap reference. The FSR pin controls the effective ref-
erence voltage of the ADC08D1520QML such that the differ-
ential full-scale input range at the analog inputs is a normal
amplitude with the FSR pin high, or a reduced amplitude with
FSR pin low as defined by the specification VIN in the Con-
verter Electrical Characteristics. Best SNR is obtained with
FSR high.
tJ(MAX) = (VIN(P-P)/VINFSR) x (1/(2(N+1) x π x fIN))
where tJ(MAX) is the rms total of all jitter sources in seconds,
VIN(P-P) is the peak-to-peak analog input signal, VINFSR is the
full-scale range of the ADC, "N" is the ADC resolution in bits
and fIN is the maximum input frequency, in Hertz, at the ADC
analog input.
2.4 THE CLOCK INPUTS
The ADC08D1520QML has differential LVDS clock inputs,
CLK+ and CLK-, which must be driven with an a.c. coupled,
differential clock signal. Although the ADC08D1520QML is
Note that the maximum jitter described above is the RSS sum
of the jitter from all sources, including that in the ADC input
clock, that added by the system to the ADC input clock and
39
www.national.com
input signals and that added by the ADC itself. Since the ef-
fective jitter added by the ADC is beyond user control, the best
the user can do is to keep the sum of the externally added
input clock jitter and the jitter added by the analog circuitry to
the analog signal to a minimum.
and then programmed to 1b for a minimum of tCAL_H input
clock cycles to initiate a calibration cycle. The CalRun signal
should be monitored to determine when the calibration cycle
has completed. The CalRun pin will become a logic high in-
dicating an active calibration cycle regardless of which
method was used to initiate the calibration cycle. Note that the
DCLK outputs are not active during a calibration cycle; there-
fore, it is not recommended for use as a system clock.
Input clock amplitudes above those specified in the Converter
Electrical Characteristics may result in increased input offset
voltage. This would cause the converter to produce an output
code other than the expected 127/128 when both input pins
are at the same potential.
The minimum number of tCAL_L and tCAL_H input clock cycle
sequences are required to ensure that random noise does not
cause a calibration to begin when it is not desired. As men-
tioned in 1.1 OVERVIEW, for best performance, a calibration
should be performed 20 seconds or more after power up and
repeated when the operating temperature changes signifi-
cantly relative to the specific system design performance
requirements. Dynamic performance changes slightly with in-
creasing junction temperature and can be easily corrected by
performing a calibration.
2.5 CONTROL PINS
Six control pins (without the use of the serial interface) provide
a wide range of possibilities in the operation of the AD-
C08D1520QML and facilitate its use. These control pins pro-
vide Full-Scale Input Range setting, Self Calibration, Output
Edge Synchronization choice, LVDS Output Level choice and
a Power Down feature.
2.5.1 Full-Scale Input Range Setting
2.5.3 Output Edge Synchronization
The input full-scale range can be selected with the FSR con-
trol input (pin 14) in the Normal Mode of operation. The input
full-scale range is specified as VIN in the Converter Electrical
Characteristics. In the Extended Control Mode, the input full-
scale range may be programmed using the Full-Scale Adjust
Voltage register. See 2.3 THE ANALOG INPUT for more in-
formation.
DCLK signals are available to help latch the converter output
data into external circuitry. The output data can be synchro-
nized with either edge of these DCLK signals. That is, the
output data transition can be set to occur with either the rising
edge or the falling edge of the DCLK signal, so that either
edge of that DCLK signal can be used to latch the output data
into the receiving circuit.
When OutEdge (pin 4) is high, the output data is synchronized
with (changes with) the rising edge of the DCLK+ (pin 82).
When OutEdge is low, the output data is synchronized with
the falling edge of DCLK+.
2.5.2 Calibration
The ADC08D1520QML calibration must be run to achieve
specified performance. The calibration must be initiated by
the user. The calibration procedure is exactly the same
whether there is an input clock present upon power up or if
the clock begins some time after application of power. The
CalRun output indicator is high while a calibration is in
progress. Note that the DCLK outputs are not active during a
calibration cycle by default, therefore it is not recommended
for use as a system clock. The DCLK outputs are continuously
present at the output only when the Resistor Trim Disable is
activated.
At the very high speeds of which the ADC08D1520QML is
capable, slight differences in the lengths of the DCLK and
data lines can mean the difference between successful and
erroneous data capture. The OutEdge pin is used to capture
data on the DCLK edge that best suits the application circuit
and layout.
2.5.4 LVDS Output Level Control
The output level can be set to one of two levels with OutV
(pin3). The strength of the output drivers is greater with OutV
high. With OutV low there is less power consumption in the
output drivers, but the lower output level means decreased
noise immunity.
2.5.2.1 Initiating Calibration
A calibration may be run at any time in both the Non-DES and
DES Modes. After power-up, we recommend that the part be
calibrated with the Resistor Trim Disable inactive once the
power supplies have stabilized and the temperature of the
chip has stabilized. When a calibration is run with the Resistor
Trim Disable inactive, both the ADC and the input termination
resistor are calibrated. However, since the input termination
resistance changes only marginally with temperature, the us-
er has the option to disable the input termination resistor
calibration for subsequent calibrations, which will guarantee
that the DCLK is continuously present at the output. The Re-
sistor Trim Disable can be programmed in the Extended
Configuration register (Addr: 9h) when in the Extended Con-
trol Mode. Refer to Extended Configuration Register for reg-
ister programming information.
For short LVDS lines and low noise systems, satisfactory per-
formance may be realized with the OutV input low. If the LVDS
lines are long and/or the system in which the AD-
C08D1520QML is used is noisy, it may be necessary to tie
the OutV pin high.
2.5.5 Dual Edge Sampling
The Dual Edge Sampling (DES) feature causes one of the two
input pairs to be routed to both ADCs. The other input pair is
deactivated. One of the ADCs samples the input signal on the
rising input clock edge (duty cycle corrected), the other sam-
ples the input signal on the falling input clock edge (duty cycle
corrected). If the device is in the 1:4 Demux DES Mode, the
result is an output data rate 1/4 that of the interleaved sample
rate which is twice the input clock frequency. Data is present-
ed in parallel on all four output buses in the following order:
DQd, DId, DQ, DI. If the device is the Non-Demultiplex output
mode, the result is an output data rate 1/2 that of the inter-
leaved sample rate. Data is presented in parallel on two
output buses in the following order: DQ, DI.
As dynamic performance changes slightly with junction tem-
perature, a calibration may be executed to bring the perfor-
mance of the ADC in line. Two methods can be used initiate
a calibration. The first method is to hold the CAL pin low for
at least tCAL_L input clock cycles, then hold it high for at least
another tCAL_H input clock cycles. The second method is to
program the CAL bit in the Calibration register while in Ex-
tended Control Mode. The functionality of the CAL bit is
exactly the same as using the CAL pin. The CAL bit must be
programmed to 0b for a minimum of tCAL_Linput clock cycles
www.national.com
40
To use this feature in the Non-Extended Control Mode, tie pin
127 to VA/2 and the signal at the I- channel input will be sam-
pled by both converters.
centimeter. Leadless chip capacitors are preferred because
they have low lead inductance.
The VA and VDR supply pins should be isolated from each
other to prevent any digital noise from being coupled into the
analog portions of the ADC. A ferrite choke, such as the JW
Miller FB20009-3B, is recommended between these supply
lines when a common source is used for them.
In the Extended Control Mode, either input may be used for
dual edge sampling. See 1.1.5.1 Dual-Edge Sampling.
2.5.6 Power Down Feature
The Power Down pins (PD and PDQ) allow the AD-
C08D1520QML to be entirely powered down (PD) or the Q-
Channel channel to be powered down and the I- Channel to
remain active. See 1.1.7 Power Down for details on the power
down feature.
As is the case with all high speed converters, the AD-
C08D1520QML should be assumed to have little power sup-
ply noise rejection. Any power supply used for digital circuitry
in a system where a lot of digital power is being consumed
should not be used to supply power to the ADC08D1520QML.
The ADC supplies should be the same supply used for other
analog circuitry, if not a dedicated supply.
The digital data (+/-) output pins are put into a high impedance
state when the PD pin for the respective channel is high. Upon
return to normal operation, the pipeline will contain meaning-
less information and must be flushed.
2.7.1 Supply Voltage
The ADC08D1520QML is specified to operate with a supply
voltage of 1.9V ±0.1V. It is very important to note that, while
this device will function with slightly higher supply voltages,
these higher supply voltages may reduce product lifetime.
If the PD input is brought high while a calibration is running,
the device will not go into power down until the calibration
sequence is complete. However, if power is applied and PD
is simultaneously ramped, the device will not calibrate until
the PD input goes low. When PD is high and a calibration is
initiated, the request for calibration is completely ignored. Re-
fer to 1.1.7 Power Down
No pin should ever have a voltage on it that is in excess of the
supply voltage or below ground by more than 150 mV, not
even on a transient basis. This can be a problem upon appli-
cation of power and power shut-down. Be sure that the sup-
plies to circuits driving any of the input pins, analog or digital,
do not come up any faster than does the voltage at the AD-
C08D1520QML power pins.
2.6 THE DIGITAL OUTPUTS
The ADC08D1520QML demultiplexes the output data of each
of the two ADCs on the die onto two LVDS output buses (total
of four buses, two for each ADC). For each of the two con-
verters, the results of successive conversions started on the
odd falling edges of the CLK+ pin are available on one of the
two LVDS buses, while the results of conversions started on
the even falling edges of the CLK+ pin are available on the
other LVDS bus. This means that, the word rate at each LVDS
bus is 1/2 the ADC08D1520QML input clock rate and the two
buses must be multiplexed to obtain the entire 1.5 GSPS
conversion result.
The Absolute Maximum Ratings should be strictly observed,
even during power up and power down. A power supply that
produces a voltage spike at turn-on and/or turn-off of power
can destroy the ADC08D1520QML. The circuit of Figure 15
will provide supply overshoot protection.
Many linear regulators will produce output spiking at power-
on unless there is a minimum load provided. Active devices
draw very little current until their supply voltages reach a few
hundred millivolts. The result can be a turn-on spike that can
destroy the ADC08D1520QML, unless a minimum load is
provided for the supply. The 100Ω resistor at the regulator
output provides a minimum output current during power-up to
ensure there is no turn-on spiking.
Since the minimum recommended input clock rate for this
device is 200 MSPS (Non DES Mode), the effective rate can
be reduced to as low as 100 MSPS by using the results avail-
able on just one of the two LVDS buses and a 200 MHz input
clock, decimating the 200 MSPS data by two.
In the circuit of Figure 15, an LM317 linear regulator is satis-
factory if its input supply voltage is 4V to 5V . If a 3.3V supply
is used, an LM1086 linear regulator is recommended.
There is one LVDS output clock pair (DCLK+/-) available for
use to latch the LVDS outputs on all buses. Whether the data
is sent at the rising or falling edge of DCLK is determined by
the sense of the OutEdge pin, as described in 2.5.3 Output
Edge Synchronization.
DDR (Double Data Rate) clocking can also be used. In this
mode a word of data is presented with each edge of DCLK,
reducing the DCLK frequency to 1/4 the input clock frequency.
See the Timing Diagram section for details.
The OutV pin is used to set the LVDS differential output levels.
See 2.5.4 LVDS Output Level Control.
The output format is Offset Binary. Accordingly, a full-scale
input level with VIN+ positive with respect to VIN− will produce
an output code of all ones, a full-scale input level with VIN−
positive with respect to VIN+ will produce an output code of all
zeros and when VIN+ and VIN− are equal, the output code will
vary between codes 127 and 128.
30024754
FIGURE 15. Non-Spiking Power Supply
The output drivers should have a supply voltage, VDR, that is
within the range specified in the Operating Ratings table. This
voltage should not exceed the VA supply voltage.
2.7 POWER CONSIDERATIONS
If the power is applied to the device without an input clock
signal present, the current drawn by the device might be be-
low 200 mA. This is because the ADC08D1520QML gets
reset through clocked logic and its initial state is unknown. If
the reset logic comes up in the "on" state, it will cause most
of the analog circuitry to be powered down, resulting in less
A/D converters draw sufficient transient current to corrupt
their own power supplies if not adequately bypassed. A 33 µF
capacitor should be placed within an inch (2.5 cm) of the A/D
converter power pins. A 0.1 µF capacitor should be placed as
close as possible to each VA pin, preferably within one-half
41
www.national.com
than 100 mA of current draw. This current is greater than the
power down current because not all of the ADC is powered
down. The device current will be normal after the input clock
is established.
top and bottom copper areas. These thermal vias act as "heat
pipes" to carry the thermal energy from the device side of the
board to the opposite side of the board where it can be more
effectively dissipated. The use of approximately 100 thermal
vias is recommended. Use of a higher weight copper on the
internal ground plane is recommended, (i.e. 2OZ instead of
1OZ, for thermal considerations only.
2.7.2 Thermal Management
The ADC08D1520QML is capable of impressive speeds and
performance at very low power levels for its speed. However,
the power consumption is still high enough to require attention
to thermal management. For reliability reasons, the die tem-
perature should be kept to a maximum of 150°C. That is, TA
(ambient temperature) plus ADC power consumption times
θJA (junction to ambient thermal resistance) should not ex-
ceed 150°C.
The thermal vias should be placed on a 61mil grid spacing
and have a diameter of 15 mil typically. These vias should be
barrel plated to avoid solder wicking into the vias during the
soldering process as this wicking could cause voids in the
solder between the package exposed pad and the thermal
land on the PCB. Such voids could increase the thermal re-
sistance between the device and the thermal land on the
board, which would cause the device to run hotter.
Please note that the following are recommendations for
mounting this device onto a PCB. This should be considered
the starting point in PCB and assembly process development.
It is recommended that the process be developed based upon
past experience in package mounting.
If it is desired to monitor die temperature, a temperature sen-
sor may be mounted on the heat sink area of the board near
the thermal vias. Allow for a thermal gradient between the
temperature sensor and the ADC08D1520QML die of θJ-PAD
times typical power consumption.
The bottom of the package of the ADC08D1520QML provides
the primary heat removal path as well as excellent electrical
grounding to the printed circuit board. The land pattern design
for lead attachment to the PCB should be the same as for a
conventional LQFP, but the bottom of the package must be
attached to the board to remove the maximum amount of heat
from the package, as well as to ensure best product para-
metric performance.
2.8 LAYOUT AND GROUNDING
Proper grounding and proper routing of all signals are essen-
tial to ensure accurate conversion. A single ground plane
should be used, instead of splitting the ground plane into ana-
log and digital areas.
Since digital switching transients are composed largely of
high frequency components, the skin effect tells us that total
ground plane copper weight will have little effect upon the
logic-generated noise. Total surface area is more important
than is total ground plane volume. Coupling between the typ-
ically noisy digital circuitry and the sensitive analog circuitry
can lead to poor performance that may seem impossible to
isolate and remedy. The solution is to keep the analog cir-
cuitry well separated from the digital circuitry.
To maximize the removal of heat from the package, a thermal
land pattern must be incorporated on the PC board within the
footprint of the package. The bottom of the device must be
soldered down to ensure adequate heat conduction out of the
package. The land pattern for this exposed pad should be as
large as the 600 x 600 mil bottom of the package and be lo-
cated such that the bottom of the device is entirely over that
thermal land pattern. This thermal land pattern should be
electrically connected to ground.
High power digital components should not be located on or
near any linear component or power supply trace or plane that
services analog or mixed signal components as the resulting
common return current path could cause fluctuation in the
analog input “ground” return of the ADC, causing excessive
noise in the conversion result.
Generally, we assume that analog and digital lines should
cross each other at 90° to avoid getting digital noise into the
analog path. In high frequency systems, however, avoid
crossing analog and digital lines altogether. The input clock
lines should be isolated from ALL other lines, analog AND
digital. The generally accepted 90° crossing should be avoid-
ed as even a little coupling can cause problems at high
frequencies. Best performance at high frequencies is ob-
tained with a straight signal path.
The analog input should be isolated from noisy signal traces
to avoid coupling of spurious signals into the input. This is
especially important with the low level drive required of the
ADC08D1520QML. Any external component (e.g., a filter ca-
pacitor) connected between the converter's input and ground
should be connected to a very clean point in the analog
ground plane. All analog circuitry (input amplifiers, filters, etc.)
should be separated from any digital components.
30024721
FIGURE 16. Recommended Package Land Pattern
Since a large aperture opening may result in poor release, the
aperture opening should be subdivided into an array of small-
er openings, similar to the land pattern of Figure 16.
2.9 DYNAMIC PERFORMANCE
To minimize junction temperature, it is recommended that a
simple heat sink be built into the PCB. This is done by includ-
ing a copper area of about 2.25 square inches (14.52 square
cm) on the opposite side of the PCB. This copper area may
be plated or solder coated to prevent corrosion, but should
not have a conformal coating, which could provide some ther-
mal insulation. Thermal vias should be used to connect these
The ADC08D1520QML is a.c. tested and its dynamic perfor-
mance is guaranteed. To meet the published specifications
and avoid jitter-induced noise, the clock source driving the
CLK input must exhibit low rms jitter. The allowable jitter is a
function of the input frequency and the input signal level, as
described in 2.4 THE CLOCK INPUTS.
www.national.com
42
It is good practice to keep the ADC input clock line as short
as possible, to keep it well away from any other signals and
to treat it as a transmission line. Other signals can introduce
jitter into the input clock signal. The clock signal can also in-
troduce noise into the analog path if not isolated from that
path.
When in Normal Mode, Pin 127 must be tied high. If pin 127
is tied to VA/2, the converter performs dual edge sampling
(DES).
TABLE 10. Extended Control Mode Operation (Pin 41
Logic Low and Pin 52 VA/2 or Logic High)
Pin
3
Function
Best dynamic performance is obtained when the exposed pad
at the back of the package has a good connection to ground.
This is because this path from the die to ground is a lower
impedance than offered by the package pins.
SCLK (Serial Clock)
4
SDATA (Serial Data)
127
SCS (Serial Interface Chip Select)
2.10 USING THE SERIAL INTERFACE
2.11 COMMON APPLICATION PITFALLS
The ADC08D1520QML may be operated in the Non-Extend-
ed Control (non-Serial Interface) Mode or in the extended
control mode. Table 9 and Table 10 describe the functions of
pins 3, 4, 14 and 127 in the Non-Extended Control Mode and
the Extended Control Mode, respectively.
Driving the inputs (analog or digital) beyond the power
supply rails. For device reliability, no input should go more
than 150 mV below the ground pins or 150 mV above the
supply pins. Exceeding these limits on even a transient basis
may not only cause faulty or erratic operation, but may impair
device reliability. It is not uncommon for high speed digital
circuits to exhibit undershoot that goes more than a volt below
ground. Controlling the impedance of high speed lines and
terminating these lines in their characteristic impedance
should control overshoot.
2.10.1 Non-Extended Control Mode Operation
Non-extended Control Mode operation means that the Serial
Interface is not active and all controllable functions are con-
trolled with various pin settings. Pin 41 is the primary control
of the extended control enable function. When pin 41 is logic
high, the device is in the Non-Extended Control Mode. If pin
41 is tied to VA/2 and pin 52 connected to VA/2 or logic high,
the extended control enable function is controlled by pin 14.
The device has functions which are pin programmable when
in the Non-Extended Control Mode. An example is the full-
scale range is controlled in the Non-Extended Control Mode
by setting pin 14 high or low. Table 9 indicates the pin func-
tions of the ADC08D1520QML in the Non-Extended Control
Mode.
Care should be taken not to overdrive the inputs of the AD-
C08D1520QML. Such practice may lead to conversion inac-
curacies and even to device damage.
Driving the VBG pin to change the reference voltage. As
mentioned in 2.2 THE REFERENCE VOLTAGE, the refer-
ence voltage is intended to be fixed to provide one of two
different full-scale values (650 mVP-P and 870 mVP-P). Over
driving this pin will not change the full scale value, but can be
used to change the LVDS common mode voltage from 0.8V
to 1.2V by tying the VBG pin to VA.
TABLE 9. Non-Extended Control Mode Operation
(Pin 41 VA/2 and Pin 52 VA/2 or Logic High)
Driving the clock input with an excessively high level
signal. The ADC input clock level should not exceed the level
described in the Operating Ratings Table or the input offset
could change.
VA/2
n/a
Pin
3
Low
Reduced VOD
OutEdge = Neg
N/A
High
Normal VOD
OutEdge = Pos
N/A
4
DDR
DES
Inadequate input clock levels. As described in 2.4 THE
CLOCK INPUTS, insufficient input clock levels can result in
poor performance. Excessive input clock levels could result
in the introduction of an input offset.
127
Extended
Control
Mode
Reduced VIN
Normal VIN
14
Using a clock source with excessive jitter, using an ex-
cessively long input clock signal trace, or having other
signals coupled to the input clock signal trace. This will
cause the sampling interval to vary, causing excessive output
noise and a reduction in SNR performance.
Pin 3 can be either high or low in the Non-Extended Control
Mode. See 1.2 NON-EXTENDED CONTROL/EXTENDED
CONTROL for more information.
Failure to provide adequate heat removal. As described in
2.7.2 Thermal Management, it is important to provide ade-
quate heat removal to ensure device reliability. This can be
done either with adequate air flow or the use of a simple heat
sink built into the board. The backside pad should be ground-
ed for best performance.
Pin 4 can be high or low in the Non-Extended Control Mode.
In the Non-Extended Control Mode, pin 4 high or low defines
the edge at which the output data transitions. See 2.5.3 Out-
put Edge Synchronization for more information. If this pin is
tied to VA/2, the output clock (DCLK) is a DDR (Double Data
Rate) clock (see 1.1.5.3 Double Data Rate) and the output
edge synchronization is irrelevant since data is clocked out
on both DCLK edges.
43
www.national.com
Revision History
Date
Released
Revision Section
Originator
Changes
01/09/08
A
B
Initial Release, New Product
Whole data sheet
R. Eddy/R.
Rennie
New Product Data Sheet, Released at Edit
16
03/05/08
R. Rennie
Edit clarification Updates, Revision A will be
Archived.
www.national.com
44
Physical Dimensions inches (millimeters) unless otherwise noted
NOTES: UNLESS OTHERWISE SPECIFIED
REFERENCE JEDEC REGISTRATION MS-026, VARIATION BFB.
128-Lead Ceramic Quad
(Gold Lead Finish)
NS Package Number EL128A
45
www.national.com
Notes
For more National Semiconductor product information and proven design tools, visit the following Web sites at:
Products
www.national.com/amplifiers
Design Support
Amplifiers
WEBENCH
www.national.com/webench
www.national.com/AU
Audio
www.national.com/audio
www.national.com/timing
www.national.com/adc
Analog University
App Notes
Clock Conditioners
Data Converters
Displays
www.national.com/appnotes
www.national.com/contacts
www.national.com/quality/green
www.national.com/packaging
Distributors
www.national.com/displays
www.national.com/ethernet
www.national.com/interface
www.national.com/lvds
Green Compliance
Packaging
Ethernet
Interface
Quality and Reliability www.national.com/quality
LVDS
Reference Designs
Feedback
www.national.com/refdesigns
www.national.com/feedback
Power Management
Switching Regulators
LDOs
www.national.com/power
www.national.com/switchers
www.national.com/ldo
LED Lighting
PowerWise
www.national.com/led
www.national.com/powerwise
Serial Digital Interface (SDI) www.national.com/sdi
Temperature Sensors
Wireless (PLL/VCO)
www.national.com/tempsensors
www.national.com/wireless
THE CONTENTS OF THIS DOCUMENT ARE PROVIDED IN CONNECTION WITH NATIONAL SEMICONDUCTOR CORPORATION
(“NATIONAL”) PRODUCTS. NATIONAL MAKES NO REPRESENTATIONS OR WARRANTIES WITH RESPECT TO THE ACCURACY
OR COMPLETENESS OF THE CONTENTS OF THIS PUBLICATION AND RESERVES THE RIGHT TO MAKE CHANGES TO
SPECIFICATIONS AND PRODUCT DESCRIPTIONS AT ANY TIME WITHOUT NOTICE. NO LICENSE, WHETHER EXPRESS,
IMPLIED, ARISING BY ESTOPPEL OR OTHERWISE, TO ANY INTELLECTUAL PROPERTY RIGHTS IS GRANTED BY THIS
DOCUMENT.
TESTING AND OTHER QUALITY CONTROLS ARE USED TO THE EXTENT NATIONAL DEEMS NECESSARY TO SUPPORT
NATIONAL’S PRODUCT WARRANTY. EXCEPT WHERE MANDATED BY GOVERNMENT REQUIREMENTS, TESTING OF ALL
PARAMETERS OF EACH PRODUCT IS NOT NECESSARILY PERFORMED. NATIONAL ASSUMES NO LIABILITY FOR
APPLICATIONS ASSISTANCE OR BUYER PRODUCT DESIGN. BUYERS ARE RESPONSIBLE FOR THEIR PRODUCTS AND
APPLICATIONS USING NATIONAL COMPONENTS. PRIOR TO USING OR DISTRIBUTING ANY PRODUCTS THAT INCLUDE
NATIONAL COMPONENTS, BUYERS SHOULD PROVIDE ADEQUATE DESIGN, TESTING AND OPERATING SAFEGUARDS.
EXCEPT AS PROVIDED IN NATIONAL’S TERMS AND CONDITIONS OF SALE FOR SUCH PRODUCTS, NATIONAL ASSUMES NO
LIABILITY WHATSOEVER, AND NATIONAL DISCLAIMS ANY EXPRESS OR IMPLIED WARRANTY RELATING TO THE SALE
AND/OR USE OF NATIONAL PRODUCTS INCLUDING LIABILITY OR WARRANTIES RELATING TO FITNESS FOR A PARTICULAR
PURPOSE, MERCHANTABILITY, OR INFRINGEMENT OF ANY PATENT, COPYRIGHT OR OTHER INTELLECTUAL PROPERTY
RIGHT.
LIFE SUPPORT POLICY
NATIONAL’S PRODUCTS ARE NOT AUTHORIZED FOR USE AS CRITICAL COMPONENTS IN LIFE SUPPORT DEVICES OR
SYSTEMS WITHOUT THE EXPRESS PRIOR WRITTEN APPROVAL OF THE CHIEF EXECUTIVE OFFICER AND GENERAL
COUNSEL OF NATIONAL SEMICONDUCTOR CORPORATION. As used herein:
Life support devices or systems are devices which (a) are intended for surgical implant into the body, or (b) support or sustain life and
whose failure to perform when properly used in accordance with instructions for use provided in the labeling can be reasonably expected
to result in a significant injury to the user. A critical component is any component in a life support device or system whose failure to perform
can be reasonably expected to cause the failure of the life support device or system or to affect its safety or effectiveness.
National Semiconductor and the National Semiconductor logo are registered trademarks of National Semiconductor Corporation. All other
brand or product names may be trademarks or registered trademarks of their respective holders.
Copyright© 2008 National Semiconductor Corporation
For the most current product information visit us at www.national.com
National Semiconductor
Americas Technical
Support Center
Email:
new.feedback@nsc.com
Tel: 1-800-272-9959
National Semiconductor Europe
Technical Support Center
Email: europe.support@nsc.com
German Tel: +49 (0) 180 5010 771
English Tel: +44 (0) 870 850 4288
National Semiconductor Asia
Pacific Technical Support Center
Email: ap.support@nsc.com
National Semiconductor Japan
Technical Support Center
Email: jpn.feedback@nsc.com
www.national.com
ADC08D1520WGFQV 替代型号
型号 | 制造商 | 描述 | 替代类型 | 文档 |
5962F0721401VZC | TI | 耐辐射加固保障 (RHA)、QMLV、300krad、陶瓷、8 位、双通道 1.5GSPS | 功能相似 |
ADC08D1520WGFQV 相关器件
型号 | 制造商 | 描述 | 价格 | 文档 |
ADC08D1520WGMPR | TI | 耐辐射加固保障 (RHA)、QMLV、300krad、陶瓷、8 位、双通道 1.5GSPS 或单通道 3GSPS ADC | NBC | 128 | 25 to 25 | 获取价格 | |
ADC08D1520_09 | NSC | Low Power, 8-Bit, Dual 1.5 GSPS or Single 3.0 GSPS A/D Converter | 获取价格 | |
ADC08D500 | ADI | High Performance, Low Power, Dual 8-Bit, 500 MSPS A/D Converter | 获取价格 | |
ADC08D500 | NSC | High Performance, Low Power, Dual 8-Bit, 500 MSPS A/D Converter | 获取价格 | |
ADC08D500 | TI | 8 位、双路 500MSPS 或单路 1.0GSPS 模数转换器 (ADC) | 获取价格 | |
ADC08D500CIYB | ADI | High Performance, Low Power, Dual 8-Bit, 500 MSPS A/D Converter | 获取价格 | |
ADC08D500CIYB | NSC | High Performance, Low Power, Dual 8-Bit, 500 MSPS A/D Converter | 获取价格 | |
ADC08D500CIYB/NOPB | TI | 8 位、双路 500MSPS 或单路 1.0GSPS 模数转换器 (ADC) | NNB | 128 | -40 to 85 | 获取价格 | |
ADC08D500DEV | NSC | High Performance, Low Power, Dual 8-Bit, 500 MSPS A/D Converter | 获取价格 | |
ADC08D500EVAL | ADI | High Performance, Low Power, Dual 8-Bit, 500 MSPS A/D Converter | 获取价格 |
ADC08D1520WGFQV 相关文章
- 2024-09-20
- 6
- 2024-09-20
- 9
- 2024-09-20
- 8
- 2024-09-20
- 6