NE567T [NXP]
IC TELECOM, TONE DECODER CIRCUIT, MBCY8, Telecom Signaling Circuit;
| 型号： | NE567T |
| 厂家： | 
NXP |
| 描述： | IC TELECOM, TONE DECODER CIRCUIT, MBCY8, Telecom Signaling Circuit 解码器 |
| 文件： | 总13页 (文件大小：166K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
Philips Semiconductors Linear Products
Product specification
Tone decoder/phase-locked loop
NE/SE567
DESCRIPTION
PIN CONFIGURATIONS
The NE/SE567 tone and frequency decoder is a highly stable
phase-locked loop with synchronous AM lock detection and power
output circuitry. Its primary function is to drive a load whenever a
sustained frequency within its detection band is present at the
self-biased input. The bandwidth center frequency and output delay
are independently determined by means of four external
components.
FE, D, N Packages
OUTPUT FILTER
CAPACITOR C3
OUTPUT
GROUND
TIMING
ELEMENTS R1
AND C1
1
2
3
4
8
7
6
5
LOW-PASS FILTER
CAPACITOR C2
INPUT
SUPPLY VOLTAGE V+
TIMING ELEMENT R1
TOP VIEW
FEATURES
F Package
• Wide frequency range (.01Hz to 500kHz)
1
2
3
4
5
6
7
14
13
12
11
10
9
OUTPUT
C3
GND
• High stability of center frequency
NC
• Independently controllable bandwidth (up to 14%)
• High out-band signal and noise rejection
• Logic-compatible output with 100mA current sinking capability
• Inherent immunity to false signals
NC
C2
NC
R1C1
INPUT
NC
R1
• Frequency adjustment over a 20-to-1 range with an external
NC
NC
resistor
V
8
CC
• Military processing available
TOP VIEW
• Frequency monitoring and control
• Wireless intercom
APPLICATIONS
• Touch-Tone decoding
• Precision oscillator
• Carrier current remote controls
• Ultrasonic controls (remote TV, etc.)
• Communications paging
BLOCK DIAGRAM
4
R
2
3.9k
3
PHASE
DETECTOR
2
INPUT
V1
R
1
LOOP
LOW
5
6
CURRENT
CONTROLLED
OSCILLATOR
PASS
AMP
FILTER
C
2
C
1
R
3
+
–
8
AMP
QUADRATURE
PHASE
DETECTOR
R
V
L
REF
+V
7
1
C
OUTPUT
FILTER
3
Touch-Tone is a registered trademark of AT&T.
403
April 15, 1992
853-0124 06456
Philips Semiconductors Linear Products
Product specification
Tone decoder/phase-locked loop
NE/SE567
EQUIVALENT SCHEMATIC
404
April 15, 1992
Philips Semiconductors Linear Products
Product specification
Tone decoder/phase-locked loop
NE/SE567
ORDERING INFORMATION
DESCRIPTION
TEMPERATURE RANGE
0 to +70°C
ORDER CODE
DWG #
0174C
0581B
0404B
0174C
0581B
0404B
8-Pin Plastic SO
14-Pin Cerdip
NE567D
NE567F
NE567N
SE567D
SE567FE
SE567N
0 to +70°C
8-Pin Plastic DIP
8-Pin Plastic SO
8-Pin Cerdip
0 to +70°C
-55°C to +125°C
-55°C to +125°C
-55°C to +125°C
8-Pin Plastic DIP
ABSOLUTE MAXIMUM RATINGS
SYMBOL
PARAMETER
RATING
UNIT
T
A
Operating temperature
NE567
0 to +70
-55 to +125
10
°C
°C
V
SE567
V
CC
Operating voltage
V+
V-
Positive voltage at input
Negative voltage at input
Output voltage (collector of output transistor)
Storage temperature range
Power dissipation
0.5 +V
-10
V
S
V
DC
V
DC
V
OUT
15
T
STG
-65 to +150
300
°C
mW
P
D
405
April 15, 1992
Philips Semiconductors Linear Products
Product specification
Tone decoder/phase-locked loop
NE/SE567
DC ELECTRICAL CHARACTERISTICS
V +=5.0V; T =25°C, unless otherwise specified.
A
SYM-
PARAMETER
BOL
TEST CONDITIONS
SE567
Typ
NE567
Typ
UNIT
Max
Min
Max
Min
Center frequency1
f
f
Highest center frequency
500
35 ±140
35 ±60
0
500
35 ±140
35 ±60
0
kHz
O
O
2
Center frequency stability
-55 to +125°C
0 to +70°C
ppm/°C
ppm/°C
f
Center frequency distribution
-10
+10
1
-10
+10
2
%
1
O
O
fO + 100kHz +
1.1R1C1
f
Center frequency shift with supply
voltage
0.5
14
0.7
14
%/V
1
fO + 100kHz +
1.1R1C1
Detection bandwidth
BW
Largest detection bandwidth
12
16
4
10
18
6
% of f
% of f
1
O
fO + 100kHz +
1.1R1C1
BW
BW
Largest detection bandwidth skew
Largest detection bandwidth—
variation with temperature
2
3
O
V =300mV
±0.1
±0.1
%/°C
I
RMS
BW
Largest detection bandwidth—
variation with supply voltage
V =300mV
±2
±2
%/V
I
RMS
Input
R
Input resistance
15
10
20
20
15
+6
25
25
15
10
20
20
15
+6
25
25
kΩ
IN
4
V
I
Smallest detectable input voltage
I =100mA, f =f
mV
L
I
O
RMS
RMS
4
Largest no-output input voltage
I =100mA, f =f
mV
L
I
O
Greatest simultaneous out-band
signal-to-in-band signal ratio
dB
Minimum input signal to wide-band
noise ratio
B =140kHz
n
-6
-6
dB
Output
Fastest on-off cycling rate
“1” output leakage current
“0” output voltage
f /20
f /20
O
O
V =15V
0.01
0.2
0.6
30
25
0.4
1.0
0.01
0.2
0.6
30
25
0.4
1.0
µA
V
8
I =30mA
L
I =100mA
L
V
3
t
t
Output fall time
R =50Ω
L
ns
ns
F
3
Output rise time
R =50Ω
L
150
150
R
General
V
Operating voltage range
Supply current quiescent
Supply current—activated
Quiescent power dissipation
4.75
9.0
8
4.75
9.0
10
15
V
CC
6
7
mA
mA
mW
R =20kΩ
L
11
30
13
12
35
t
PD
NOTES:
1. Frequency determining resistor R should be between 2 and 20kΩ
1
2. Applicable over 4.75V to 5.75V. See graphs for more detailed information.
3. Pin 8 to Pin 1 feedback R network selected to eliminate pulsing during turn-on and turn-off.
L
4. With R =130kΩ from Pin 1 to V+. See Figure 1.
2
406
April 15, 1992
Philips Semiconductors Linear Products
Product specification
Tone decoder/phase-locked loop
NE/SE567
TYPICAL PERFORMANCE CHARACTERISTICS
Bandwidth vs Input
Signal Amplitude
Largest Detection bandwidth
vs Operating Frequency
Detection bandwidth as a
Function of C and C
2
3
6
5
4
300
250
200
150
100
50
15
10
5
10
10
10
C
C
3
2
3
0
0
10
0
2
4
6
8
10 12 14 16
0
2
4
6
8
10 12 14 16
0.1
1
10
100
1000
CENTER FREQUENCY — kHz
BANDWIDTH — % OF f
BANDWIDTH — % OF f
O
O
Typical Supply Current vs
Supply Voltage
Greatest Number of Cycles
Before Output
Typical Output Voltage vs
Temperature
1.0
0.9
0.8
0.7
0.6
0.5
0.4
0.3
0.2
0.1
0
1000
500
300
100
50
25
20
15
10
5
I
= 100mA
L
BANDWIDTH LIMITED BY
EXTERNAL RESISTOR
NO LOAD
“ON” CURRENT
(MINIMUM C
)
2
QUIESCENT
CURRENT
I
= 30mA
L
BANDWIDTH
30
LIMITED BY (C
)
2
0
10
4
5
6
7
8
9
10
1
5
10
50
100
–75
–25
0
25
75
125
BANDWIDTH — % OF f
O
SUPPLY VOLTAGE — V
TEMPERATURE — °C
Typical Frequency Drift
With Temperature
(Mean and SD)
Typical Frequency Drift
With Temperature
(Mean and SD)
Typical Frequency Drift
With Temperature
(Mean and SD)
1.5
1.0
1.5
5.5
(2)
(1)
+V = 7.0V (1)
+V = 9.0V (2)
+V = 4.75V
+V = 5.75V
1.0
0.5
2.5
0
0.5
0
0
–2.5
–5.0
–7.5
–10
–0.5
–1.0
–1.5
–0.5
–1.0
–1.5
–75
–25
0
25
75
125
–75
–25
0
25
75
125
–75
–25
0
25
75
125
TEMPERATURE — °C
TEMPERATURE — °C
TEMPERATURE — °C
407
April 15, 1992
Philips Semiconductors Linear Products
Product specification
Tone decoder/phase-locked loop
NE/SE567
TYPICAL PERFORMANCE CHARACTERISTICS (Continued)
Center Frequency
Center Frequency Temperature
Coefficient
Typical Bandwidth Variation
Shift With Supply
Voltage Change vs
Operating Frequency
Temperature
(Mean and SD)
100
0
1.0
0.9
0.8
0.7
0.6
15.0
12.5
10.0
7.5
14
12
10
8
–100
Dt
O
V
% V
t
0.5
0.4
0.3
0.2
0.1
0
O
6
4
–200
–300
5.0
∆t = 0°C to 70°C
2
2.5
0
BANDWIDTH AT 25°C
4.5
5.0
5.5
6.0
6.5
7.0
1
2
3 4
5
10
20
40
100
–25
0
25
75
125
–75
SUPPLY VOLTAGE — V
CENTER FREQUENCY — kHz
TEMPERATURE – °C
DESIGN FORMULAS
OPERATING INSTRUCTIONS
Figure 1 shows a typical connection diagram for the 567. For most
applications, the following three-step procedure will be sufficient for
1
fO
1.1R1 C1
choosing the external components R , C , C and C .
1
1
2
3
1. Select R1 and C1 for the desired center frequency. For best
temperature stability, R1 should be between 2K and 20K ohm,
and the combined temperature coefficient of the R1C1 product
should have sufficient stability over the projected temperature
range to meet the necessary requirements.
VI
BW
1070
in % of fO
fO C2
VI
200mVRMS
Where
2. Select the low-pass capacitor, C , by referring to the Bandwidth
2
V =Input voltage (V
)
I
RMS
versus Input Signal Amplitude graph. If the input amplitude
C =Low-pass filter capacitor (µF)
2
Variation is known, the appropriate value of f C necessary to
O
2
give the desired bandwidth may be found. Conversely, an area of
operation may be selected on this graph and the input level and
C2 may be adjusted accordingly. For example, constant
bandwidth operation requires that input amplitude be above
PHASE-LOCKED LOOP TERMINOLOGY CENTER
FREQUENCY (f )
O
The free-running frequency of the current controlled oscillator (CCO)
in the absence of an input signal.
200mV
. The bandwidth, as noted on the graph, is then
RMS
controlled solely by the f C product (f (Hz), C2(µF)).
O
2
O
Detection Bandwidth (BW)
The frequency range, centered about f , within which an input signal
O
above the threshold voltage (typically 20mV
) will cause a logical
RMS
zero state on the output. The detection bandwidth corresponds to
the loop capture range.
Lock Range
The largest frequency range within which an input signal above the
threshold voltage will hold a logical zero state on the output.
Detection Band Skew
A measure of how well the detection band is centered about the
center frequency, f . The skew is defined as (f
+f -2f )/2f
MAX MIN O O
O
where fmax and fmin are the frequencies corresponding to the
edges of the detection band. The skew can be reduced to zero if
necessary by means of an optional centering adjustment.
408
April 15, 1992
Philips Semiconductors Linear Products
Product specification
Tone decoder/phase-locked loop
NE/SE567
saturates; its collector voltage being less than 1.0 volt (typically
0.6V) at full output current (100mA). The voltage at Pin 2 is the
phase detector output which is a linear function of frequency over
TYPICAL RESPONSE
INPUT
the range of 0.95 to 1.05 f with a slope of about 20mV per percent
O
of frequency deviation. The average voltage at Pin 1 is, during lock,
a function of the in-band input amplitude in accordance with the
transfer characteristic given. Pin 5 is the controlled oscillator square
OUTPUT
NOTE:
wave output of magnitude (+V -2V ) (+V-1.4V) having a DC
BE
average of +V/2. A 1kΩ load may be driven from pin 5. Pin 6 is an
R
= 100Ω
L
exponential triangle of 1V
with an average DC level of +V/2. Only
P-P
Response to 100mV
Tone Burst
high impedance loads may be
RMS
OUTPUT
OUTPUT
(PIN 8)
V+
7% 14% BW
0
V
(SAT) < 1.0V
CE
INPUT
NOTES:
S/N = –6dB
3.9V
3.8V
3.7V
LOW PASS
FILTER
(PIN 2)
R
= 100Ω
L
Noise Bandwidth = 140Hz
Response to Same Input Tone Burst
With Wideband Noise
3. The value of C3 is generally non-critical. C3 sets the band edge
of a low-pass filter which attenuates frequencies outside the
detection band to eliminate spurious outputs. If C3 is too small,
frequencies just outside the detection band will switch the output
stage on and off at the beat frequency, or the output may pulse
on and off during the turn-on transient. If C3 is too large, turn-on
and turn-off of the
0.9f
O
f
1.1f
O
O
PIN 1
VOLTAGE
(AVG)
4.0
V
REF
THRESHOLD VOLTAGE
3.5
3.0
f
= f
O
1
+V
4
+V
2.5
0
100
200mVrms
IN-BAND
INPUT
VOLTAGE
INPUT
R
3
5
L
Figure 2. Typical Output Response
8
567
R
1
1
f
+
O
R
C
1
1
R
2
6
2
7
1
C
2
C
1
C
3
LOW
OUTPUT
FILTER
PASS
FILTER
Figure 1.
output stage will be delayed until the voltage on C passes the
3
threshold voltage. (Such delay may be desirable to avoid spurious
outputs due to transient frequencies.) A typical minimum value for
C is 2C .
3
2
4. Optional resistor R2 sets the threshold for the largest “no output”
input voltage. A value of 130kΩ is used to assure the tested limit
of 10mV
min. This resistor can be referenced to ground for
RMS
increased sensitivity. The explanation can be found in the
“optional controls” section which follows.
AVAILABLE OUTPUTS (Figure 1)
The primary output is the uncommitted output transistor collector,
Pin 8. When an in-band input signal is present, this transistor
409
April 15, 1992
Philips Semiconductors Linear Products
Product specification
Tone decoder/phase-locked loop
NE/SE567
cause supply voltage fluctuations which could, for example, shift the
detection band of narrow-band systems sufficiently to cause
momentary loss of lock. The result is a low-frequency oscillation into
and out of lock. Such effects can be prevented by supplying heavy
load currents from a separate supply or increasing the supply filter
capacitor.
V+
R
1
567
567 1
C
3
R
C
3
SPEED OF OPERATION
Minimum lock-up time is related to the natural frequency of the loop.
The lower it is, the longer becomes the turn-on transient. Thus,
DECREASE
SENSITIVITY
INCREASE
SENSITIVITY
maximum operating speed is obtained when C is at a minimum.
2
V+
When the signal is first applied, the phase may be such as to initially
drive the controlled oscillator away from the incoming frequency
rather than toward it. Under this condition, which is of course
unpredictable, the lock-up transient is at its worst and the theoretical
minimum lock-up time is not achievable. We must simply wait for the
transient to die out.
DECREASE
SENSITIVITY
R
A
R
2.5k
B
567 1
50k
C
INCREASE
SENSITIVITY
3
R
C
1.0k
SILICON
The following expressions give the values of C and C which allow
2
3
DIODES FOR
TEMPERATURE
COMPENSATION
(OPTIONAL)
highest operating speeds for various band center frequencies. The
minimum rate at which digital information may be detected without
information loss due to the turn-on transient or output chatter is
about 10 cycles per bit, corresponding to an information transfer rate
Figure 3. Sensitivity Adjust
of f /10 baud.
O
connected to pin 6 without affecting the CCO duty cycle or
temperature stability.
V+
V+
V+
V+
R
A
R
C
L
200 TO 1k
R
L
OPERATING PRECAUTIONS
A brief review of the following precautions will help the user achieve
the high level of performance of which the 567 is capable.
8
8
567
1
567
1
R
10k
R
L
f
R
f
f
1
1. Operation in the high input level mode (above 200mV) will free
the user from bandwidth variations due to changes in the in-band
signal amplitude. The input
stage is now limiting, however, so that out-band signals or high
noise levels can cause an apparent bandwidth reduction as the
inband signal is suppressed. Also, the limiting action will create
in-band components from sub-harmonic signals, so the 567
10k
C
3
8
R *
f
567
C
3
10k
R
A
200 TO
1k
*OPTIONAL - PERMITS
LOWER VALUE OF C
f
Figure 4. Chatter Prevention
becomes sensitive to signals at f /3, f /5, etc.
O
O
V+
2. The 567 will lock onto signals near (2n+1) f , and will give an
O
output for signals near (4n+1) f where n=0, 1, 2, etc. Thus,
O
signals at 5f and 9f can cause an unwanted output. If such
O
O
R
signals are anticipated, they should be attenuated before
reaching the 567 input.
3. Maximum immunity from noise and out-band signals is afforded
2
567 2
567
C
2
R
C
2
LOWERS f
RAISES f
O
O
in the low input level (below 200mV
) and reduced bandwidth
RMS
operating mode. However, decreased loop damping causes the
worst-case lock-up time to increase, as shown by the Greatest
Number of Cycles Before Output vs Bandwidth graph.
V+
LOWERS f
O
R
A
R
2.5k
4. Due to the high switching speeds (20ns) associated with 567
operation, care should be taken in lead routing. Lead lengths
should be kept to a minimum. The power supply should be
adequately bypassed close to the 567 with a 0.01µF or greater
capacitor; grounding paths should be carefully chosen to avoid
ground loops and unwanted voltage variations. Another factor
which must be considered is the effect of load energization on
the power supply. For example, an incandescent lamp typically
draws 10 times rated current at turn-on. This can be somewhat
greater when the output stage is made less sensitive, rejection of
third harmonics or in-band harmonics (of lower frequency
signals) is also improved.
B
567 1
50k
C
2
R
C
RAISES f
O
RAISES f
O
1.0k
SILICON
DIODES FOR
TEMPERATURE
COMPENSATION
(OPTIONAL)
Figure 5. Skew Adjust
410
April 15, 1992
Philips Semiconductors Linear Products
Product specification
Tone decoder/phase-locked loop
NE/SE567
SENSITIVITY ADJUSTMENT (Figure 3)
130
fO
C2
C3
+
+
F
F
When operated as a very narrow-band detector (less than 8
percent), both C and C are made quite large in order to improve
2
3
noise and out-band signal rejection. This will inevitably slow the
response time. If, however, the output stage is biased closer to the
threshold level, the turn-on time can be
260
fO
improved. This is accomplished by drawing additional current to
terminal 1. Under this condition, the 567 will also give an output for
lower-level signals (10mV or lower).
In cases where turn-off time can be sacrificed to achieve fast
turn-on, the optional sensitivity adjustment circuit can be used to
move the quiescent C voltage lower (closer to the threshold
3
voltage). However, sensitivity to beat frequencies, noise and
extraneous signals will be increased.
By adding current to terminal 1, the output stage is biased further
away from the threshold voltage. This is most useful when, to obtain
maximum operating speed, C and C are made very small.
2
3
Normally, frequencies just outside the detection band could cause
false outputs under this condition. By desensitizing the output stage,
the out-band beat notes do not feed through to the output stage.
Since the input level must
OPTIONAL CONTROLS (Figure 3)
The 567 has been designed so that, for most applications, no
external adjustments are required. Certain applications, however,
will be greatly facilitated if full advantage is taken of the added
control possibilities available through the use of additional external
components. In the diagrams given, typical
V+
V+
values are suggested where applicable. For best results the
resistors used, except where noted, should have the same
temperature coefficient. Ideally, silicon diodes would be
low-resistivity types, such as forward-biased transistor base-emitter
junctions. However, ordinary low-voltage diodes should be adequate
for most applications.
R
L
567
1
8
R
A
10k
250
R
f
20k
C
C
3
A
0.5k 0.9k 1.4k 1.9k 2.5k 3.2k 4.0k
200
UNLATCH
10k
V+
150
V+
20k
R
L
100
567
8
100k
UNLATCH
1
50
R
R
20k
f
0
C
3
0
2
4
6
8
10
12
14
16
DETECTION BAND — % OF f
O
NOTE:
prevents latch-up when power supply is turned on.
V+
C
A
R
A
Figure 7. Output Latching
50k
R
B
PIN 2
567
R
R
B
C
R
R
+ R
A
R
B
C
C
2
R
C
OPTIONAL SILICON
DIODES FOR
TEMPERATURE
COMPENSATION
NOTE:
130 10k
R
1300 10k
R
C
2
f
R
f
R
O
O
Adjust control for symmetry of detection band edges
about f
.
O
Figure 6. BW Reduction
411
April 15, 1992
Philips Semiconductors Linear Products
Product specification
Tone decoder/phase-locked loop
NE/SE567
CHATTER PREVENTION (Figure 4)
ALTERNATE METHOD OF BANDWIDTH
Chatter occurs in the output stage when C is relatively small, so
REDUCTION (Figure 6)
3
that the lock transient and the AC components at the quadrature
phase detector (lock detector) output cause the output stage to
move through its threshold more than once. Many loads, for
example lamps and relays, will not respond to the chatter. However,
logic may recognize the chatter as a series of outputs. By feeding
the output stage output back to its input (Pin 1) the chatter can be
eliminated. Three schemes for doing this are given in Figure 4. All
operate by feeding the first output step (either on or off) back to the
input, pushing the input past the threshold until the transient
conditions are over. It is only necessary to assure that the feedback
time constant is not so large as to prevent operation at the highest
anticipated speed. Although chatter can always be eliminated by
Although a large value of C will reduce the bandwidth, it also
2
reduces the loop damping so as to slow the circuit response time.
This may be undesirable. Bandwidth can be reduced by reducing
the loop gain. This scheme will improve damping and permit faster
operation under narrow-band conditions. Note that the reduced
impedance level at terminal 2 will require that a larger value of C be
used for a given filter cutoff
2
frequency. If more than three 567s are to be used, the network of R
B
and R can be eliminated and the R resistors connected together.
C
A
A capacitor between this junction and ground may be required to
shunt high frequency components.
making C large, the feedback circuit will enable faster operation of
3
the 567 by allowing C to be kept small. Note that if the feedback
3
OUTPUT LATCHING (Figure 7)
time constant is made quite large, a short burst at the input
frequency can be stretched into a long output pulse. This may be
useful to drive, for example, stepping relays.
To latch the output on after a signal is received, it is necessary to
provide a feedback resistor around the output stage (between Pins 8
and 1). Pin 1 is pulled up to unlatch the output stage.
DETECTION BAND CENTERING (OR SKEW)
ADJUSTMENT (Figure 5)
REDUCTION OF C1 VALUE
For precision very low-frequency applications, where the value of C
becomes large, an overall cost savings may be achieved by
1
When it is desired to alter the location of the detection band
(corresponding to the loop capture range) within the lock range, the
circuits shown above can be used. By moving the detection band to
one edge of the range, for example, input signal variations will
expand the detection band in only one direction. This may prove
useful when a strong but undesirable signal is expected on one side
inserting a voltage-follower between the R C junction and Pin 6,
1
1
so as to allow a higher value of R and a lower value of C for a
1
1
given frequency.
or the other of the center frequency. Since R also alters the duty
cycle slightly, this method may be used to obtain a precise duty
cycle when the 567 is used as an oscillator.
B
PROGRAMMING
To change the center frequency, the value of R can be changed
1
with a mechanical or solid state switch, or additional C capacitors
1
may be added by grounding them through saturating NPN
transistors.
412
April 15, 1992
Philips Semiconductors Linear Products
Product specification
Tone decoder/phase-locked loop
NE/SE567
TYPICAL APPLICATIONS
+
R
3
567
897Hz
DIGIT
1
R
2
C
2
3
3
R
+
+
1
C
C
2
1
567
770Hz
4
5
6
7
8
567
852Hz
+
+
+
+
9
0
567
941Hz
*
567
1209Hz
NOTES:
Component values (Typical)
R
R
= 26.8 to 15kΩ
= 24.7kΩ
1
2
567
1336Hz
R
C
= 20kΩ
3
1
= 0.10mF
C
C
C
= 1.0mF 5V
= 2.2mF 6V
= 250µF 6V
2
3
4
567
1477Hz
Touch-Tone Decoder
413
April 15, 1992
Philips Semiconductors Linear Products
Product specification
Tone decoder/phase-locked loop
NE/SE567
TYPICAL APPLICATIONS (Continued)
+5 TO 15V
60Hz AC LINE
50–200V
RMS
LOAD
5
6
C
4
27pF
567
R
1
3
5
–
567
8
K
1
+
6
2
1
+
500pF
R
5741
C
1
1
1:1
2.5kΩ
f
≈ 100kHz
O
C
2
Precision VLF
.006
AUDIO OUT
(IF INPUT IS
FREQUENCY
MODULATED)
C
1
C
.02
3
0.004mfd
+V
3
567
2
8
Carrier-Current Remote Control or Intercom
5
6
1
+V
R
1
INPUT SIGNAL
(>100mVrms)
C
20k
2
f
C
C
3
1
1
3
567
8
5
6
2
1
R
L
R
1
3
567
2
8
NOR
V
INPUT
O
5
6
1
+V
CHANNEL
C
C
C
8
1
2
3
OR RECEIVER
130
R’
1
C
+ C
+ C
+
(mfd)
20k
2
2
1
f
O
C
R
f
2
1
1
567
3
+ 1.12R
1
5
6
2
1
C’
C’
2
1
R’
1
24% Bandwidth Tone Decoder
OUTPUT
(INTO 1k
OHM MIN.
LOAD)
C’
C’
C’
3
1
2
100mv (pp)
SQUARE OR
50mVRMS
567
3
5
SINE INPUT
f
2
2
6
+90°
PHASE
SHIFT
Dual-Tone Decoder
R
1
C
C
1
2
NOTES:
= R /5
R
2
1
Adjust R so that φ = 90° with control midway.
1
0° to 180° Phase Shifter
NOTES:
1. Resistor and capacitor values chosen for desired frequencies and bandwidth.
2. If C3 is made large so as to delay turn-on of the top 567, decoding of sequential (f
f
) tones is possible.
1 2
414
April 15, 1992
Philips Semiconductors Linear Products
Product specification
Tone decoder/phase-locked loop
NE/SE567
TYPICAL APPLICATIONS (Continued)
+
+
R
L
R
567
6
L
567
6
567
3
2
5
8
8
80°
2
5
2
6
5
3
VCO
TERMINAL
(±6%)
CONNECT PIN 3
TO 2.8V TO
INVERT OUTPUT
f
O
R
1
R
> 1000Ω
L
R
> 1000Ω
R
L
R
1
1
10k
C
1
C
2
C
1
C
2
C
L
Oscillator With Double Frequency
Output
Precision Oscillator With 20ns
Switching
Oscillator With Quadrature Output
+
+
567
R
L
6
5
567
8
OUTPUT
R
L
567
8
3
6
5
1
1kΩ (MIN)
2
6
5
1
10kΩ
VCO
TERMINAL
(±6%)
R
1
100kΩ
R
1
C
2
C
1
DUTY
CYCLE
ADJUST
C
C
1
1
Precision Oscillator to Switch 100mA
Loads
Pulse Generator With 25% Duty Cycle
Pulse Generator
415
April 15, 1992
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