NCV33033DWR2 [ONSEMI]
Brushless DC Motor Controller; 直流无刷电机控制器
| 型号： | NCV33033DWR2 |
| 厂家： | 
ONSEMI |
| 描述： | Brushless DC Motor Controller |
| 文件： | 总27页 (文件大小：414K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
MC33033, NCV33033
Brushless DC
Motor Controller
The MC33033 is a high performance second generation, limited
feature, monolithic brushless dc motor controller which has evolved
from ON Semiconductor’s full featured MC33034 and MC33035
controllers. It contains all of the active functions required for the
implementation of open loop, three or four phase motor control. The
device consists of a rotor position decoder for proper commutation
sequencing, temperature compensated reference capable of supplying
sensor power, frequency programmable sawtooth oscillator, fully
accessible error amplifier, pulse width modulator comparator, three
open collector top drivers, and three high current totem pole bottom
drivers ideally suited for driving power MOSFETs. Unlike its
predecessors, it does not feature separate drive circuit supply and
ground pins, brake input, or fault output signal.
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PDIP−20
P SUFFIX
CASE 738
20
1
Included in the MC33033 are protective features consisting of
undervoltage lockout, cycle−by−cycle current limiting with a
selectable time delayed latched shutdown mode, and internal thermal
shutdown.
SO−20L
DW SUFFIX
CASE 751D
20
1
Typical motor control functions include open loop speed, forward or
reverse direction, and run enable. The MC33033 is designed to operate
brushless motors with electrical sensor phasings of 60°/300° or
120°/240°, and can also efficiently control brush dc motors.
PIN CONNECTIONS
Features
Top Drive
Output
1
20
19
18
17
16
15
14
C
B
T
T
• 10 to 30 V Operation
• Undervoltage Lockout
A
2
3
4
Output Enable
T
• 6.25 V Reference Capable of Supplying Sensor Power
• Fully Accessible Error Amplifier for Closed Loop Servo
Applications
Fwd/Rev
60°/120° Select
S
A
A
B
Bottom
Drive
Outputs
Sensor
Inputs
5
6
7
S
S
B
B
• High Current Drivers Can Control External 3−Phase MOSFET
Bridge
B
C
C
B
• Cycle−By−Cycle Current Limiting
Reference Output
Oscillator
V
CC
• Internal Thermal Shutdown
8
9
13 Gnd
• Selectable 60°/300° or 120°/240° Sensor Phasings
Error Amp
Non Inverting Input
Error Amp
Current Sense
Non Inverting Input
Error Amp Out/
PWM Input
• Also Efficiently Control Brush DC Motors with External MOSFET
12
11
H−Bridge
10
Inverting Input
• NCV Prefix for Automotive and Other Applications Requiring Site
and Control Changes
(Top View)
• Pb−Free Packages are Available
ORDERING INFORMATION
See detailed ordering and shipping information in the package
dimensions section on page 25 of this data sheet.
DEVICE MARKING INFORMATION
See general marking information in the device marking
section on page 25 of this data sheet.
©
Semiconductor Components Industries, LLC, 2007
1
Publication Order Number:
January, 2007 − Rev. 9
MC33033/D
MC33033, NCV33033
V
M
N
N
S
S
Rotor
Position
Decoder
FWR/REV
60°/120°
Enable
Motor
Undervoltage
V
CC
Output
Buffers
Lockout
Reference
Regulator
Speed
Set
Error Amp
Thermal
Shutdown
Faster
PWM
R
T
R
S
Q
Q
Oscillator
S
R
C
T
Current Sense
This device contains 266 active transistors.
Figure 1. Representative Schematic Diagram
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2
MC33033, NCV33033
MAXIMUM RATINGS
Rating
Symbol
Value
Unit
Power Supply Voltage
V
30
V
V
CC
Digital Inputs (Pins 3, 4, 5, 6, 18, 19)
−
V
ref
Oscillator Input Current (Source or Sink)
Error Amp Input Voltage Range
Error Amp Output Current
I
30
mA
V
OSC
(Pins 9, 10, Note 1)
V
−0.3 to V
10
IR
ref
(Source or Sink, Note 2)
I
mA
V
Out
Current Sense Input Voltage Range
Top Drive Voltage (Pins 1, 2, 20)
Top Drive Sink Current (Pins 1, 2, 20)
Bottom Drive Output Current
V
−0.3 to 5.0
Sense
V
40
50
V
CE(top)
I
mA
mA
Sink(top)
(Source or Sink, Pins 15,16, 17)
I
100
DRV
Electrostatic Discharge Sensitivity (ESD)
Human Body Model (HBM) Class 2, JESD22 A114−C
Machine Model (MM) Class A, JESD22 A115−A
Charged Device Model (CDM), JESD22 C101−C
−
−
−
2000
200
2000
V
V
V
Power Dissipation and Thermal Characteristics
P Suffix, Dual−In−Line, Case 738
Maximum Power Dissipation @ T = 85°C
Thermal Resistance, Junction−to−Air
DW Suffix, Surface Mount, Case 751D
P
867
75
mW
°C/W
A
D
R
θ
JA
Maximum Power Dissipation @ T = 85°C
P
619
105
mW
°C/W
A
D
Thermal Resistance, Junction−to−Air
R
θ
JA
Operating Junction Temperature
T
150
°C
°C
J
Operating Ambient Temperature Range (Note 3)
MC33033
NCV33033
T
A
−40 to +85
−40 to +125
Storage Temperature Range
T
stg
−65 to +150
°C
Stresses exceeding Maximum Ratings may damage the device. Maximum Ratings are stress ratings only. Functional operation above the
Recommended Operating Conditions is not implied. Extended exposure to stresses above the Recommended Operating Conditions may affect
device reliability.
1. The input common mode voltage or input signal voltage should not be allowed to go negative by more than 0.3 V.
2. The compliance voltage must not exceed the range of −0.3 to V
.
ref
3. NCV33033: T = −40°C, T
= 125°C. Guaranteed by design. NCV prefix is for automotive and other applications requiring site and change
low
high
control.
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3
MC33033, NCV33033
ELECTRICAL CHARACTERISTICS (V = 20 V, R = 4.7 k, C = 10 nF, T = 25°C, unless otherwise noted.)
CC
T
T
A
Characteristic
Symbol
Min
Typ
Max
Unit
REFERENCE SECTION
Reference Output Voltage (I = 1.0 mA)
V
ref
V
ref
T = 25°C
5.9
5.82
6.24
−
6.5
6.57
A
(Note 4)
Line Regulation (V = 10 V to 30 V, I = 1.0 mA)
Reg
−
−
1.5
16
30
30
−
mV
mV
mA
V
CC
ref
line
Load Regulation (I = 1.0 mA to 20 mA)
Reg
load
ref
Output Short−Circuit Current (Note 5)
Reference Under Voltage Lockout Threshold
ERROR AMPLIFIER
I
40
4.0
75
SC
V
4.5
5.0
th
Input Offset Voltage (Note 4)
V
−
−
−
0.4
10
mV
IO
Input Offset Current (Note 4)
I
8.0
−46
500
nA
nA
V
IO
Input Bias Current (Note 4)
I
−1000
IB
Input Common Mode Voltage Range
V
(0 V to V
80
ICR
ref)
Open Loop Voltage Gain (V = 3.0 V, R = 15 k)
A
VOL
70
55
65
−
−
−
dB
dB
dB
V
O
L
Input Common Mode Rejection Ratio
CMRR
86
Power Supply Rejection Ratio (V = 10 V to 30 V)
PSRR
105
CC
Output Voltage Swing
High State (R = 15 k to Gnd)
V
V
OL
4.6
−
5.3
0.5
−
1.0
L
OH
Low State (R = 17 k to V
)
ref
L
4. MC33033: T = −40°C to + 85°C; NCV33033: T = −40°C to +125°C.
A
A
5. Maximum package power dissipation limits must be observed.
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4
MC33033, NCV33033
ELECTRICAL CHARACTERISTICS (continued) (V = 20 V, R = 4.7 k, C = 10 nF, T = 25°C, unless otherwise noted.)
CC
T
T
A
Characteristic
Symbol
Min
Typ
Max
Unit
OSCILLATOR SECTION
Oscillator Frequency
f
22
−
25
0.01
4.1
28
5.0
4.5
−
kHz
%
OSC
Frequency Change with Voltage (V = 10 V to 30 V)
Δf
/ΔV
OSC
CC
Sawtooth Peak Voltage
Sawtooth Valley Voltage
LOGIC INPUTS
V
V
−
V
OSC(P)
OSC(V)
1.2
1.5
V
Input Threshold Voltage (Pins 3, 4, 5, 6, 18, 19)
V
High State
Low State
V
V
3.0
−
2.2
1.7
−
0.8
IH
IL
Sensor Inputs (Pins 4, 5, 6)
High State Input Current (V = 5.0 V)
Low State Input Current (V = 0 V)
μA
μA
I
I
−150
−600
−70
−337
−20
−150
IH
IH
IL
IL
Forward/Reverse, 60°/120° Select and Output Enable
(Pins 3, 18, 19)
High State Input Current (V = 5.0 V)
I
I
−75
−300
−36
−175
−10
−75
IH
IH
Low State Input Current (V = 0 V)
IL
IL
CURRENT−LIMIT COMPARATOR
Threshold Voltage
V
85
−
101
3.0
115
−
mV
V
th
Input Common Mode Voltage Range
Input Bias Current
V
ICR
I
−
−0.9
−5.0
μA
IB
OUTPUTS AND POWER SECTIONS
Top Drive Output Sink Saturation (I
= 25 mA)
V
−
−
0.5
1.5
V
Sink
CE(sat)
Top Drive Output Off−State Leakage (V = 30 V)
I
0.06
100
μA
ns
CE
DRV(leak)
Top Drive Output Switching Time (C = 47 pF, R = 1.0 k)
L
L
Rise Time
Fall Time
t
r
t
f
−
−
107
26
300
300
Bottom Drive Output Voltage
V
ns
V
High State (V = 30 V, I
= 50 mA)
= 50 mA)
V
V
OL
(V − 2.0)
(V − 1.1)
−
2.0
CC
source
OH
CC
CC
Low State (V = 30 V, I
−
1.5
CC
sink
Bottom Drive Output Switching Time (C = 1000 pF)
Rise Time
Fall Time
L
t
−
−
38
30
200
200
r
f
t
Under Voltage Lockout
Drive Output Enabled (V Increasing)
Hysteresis
V
8.2
0.1
8.9
0.2
10
0.3
CC
th(on)
V
H
Power Supply Current
I
−
15
22
mA
CC
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MC33033, NCV33033
100
4.0
V
T
= 20 V
CC
= 25°C
V
= 20 V
R = 4.7 k
CC
A
2.0
0
T
C
= 10 nF
T
10
−2.0
−4.0
C
= 10 nF
C = 1.0 nF
T
C
= 100 nF
T
T
0
1.0
10
100
1000
−55
−25
0
25
50
75
100
125
R , TIMING RESISTOR (kΩ)
T
T , AMBIENT TEMPERATURE (°C)
A
Figure 3. Oscillator Frequency Change
versus Temperature
Figure 2. Oscillator Frequency versus
Timing Resistor
40
56
48
40
32
0
− 0.8
−1.6
1.6
V
ref
V
T
= 20 V
CC
= 25°C
60
A
Source Saturation
(Load to Ground)
80
100
Phase
120
140
160
180
24
16
V
V
= 20 V
= 3.0 V
CC
8.0
0
Gain
O
R = 15 k
L
C = 100 pF
T
A
Sink Saturation
(Load to V )
ref
L
200
220
0.8
0
−8.0
= 25°C
Gnd
−16
−24
240
1.0 k
10 k
100 k
f, FREQUENCY (Hz)
1.0 M
10M
0
1.0
2.0
3.0
4.0
5.0
I , OUTPUT LOAD CURRENT (mA)
O
Figure 4. Error Amp Open Loop Gain and
Phase versus Frequency
Figure 5. Error Amp Output Saturation
Voltage versus Load Current
A
V
= +1.0
A
V
= +1.0
No Load
= 25°C
No Load
= 25°C
3.05
4.5
3.0
1.5
T
T
A
A
3.0
2.95
1.0 μs/DIV
5.0 μs/DIV
Figure 6. Error Amp Small−Signal
Transient Response
Figure 7. Error Amp Large−Signal
Transient Response
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MC33033, NCV33033
0
7.0
6.0
5.0
4.0
3.0
2.0
1.0
0
−4.0
−8.0
− 12
− 16
V
T
= 20 V
CC
= 25°C
No Load
T = 25°C
A
−20
−24
A
0
10
20
30
40
0
10
20
30
40
50
60
I , REFERENCE OUTPUT SOURCE CURRENT (mA)
ref
V
, SUPPLY VOLTAGE (V)
CC
Figure 9. Reference Output Voltage versus
Supply Voltage
Figure 8. Reference Output Voltage Change
versus Output Source Current
100
80
60
40
20
40
20
V
= 20 V
R = 4.7 k
CC
T
C
T
= 10 nF
= 25°C
T
A
0
−20
−40
V = 20 V
CC
No Load
0
1.0
2.0
3.0
4.0
5.0
−55
−25
0
25
50
75
100
125
0
T , AMBIENT TEMPERATURE (°C)
A
PWM INPUT VOLTAGE (V)
Figure 10. Reference Output Voltage
versus Temperature
Figure 11. Output Duty Cycle versus
PWM Input Voltage
250
1.2
0.8
V
T
= 20 V
CC
= 25°C
V = 20 V
CC
R = 1
200
150
100
A
L
C = 1.0 nF
L
T
A
= 25°C
0.4
0
50
0
1.0
2.0
3.0
4.0 5.0 6.0 7.0 8.09.010
0
10
20
30
40
V
, CURRENT SENSE INPUT VOLTAGE (NORMALIZED TO V )
th
I , SINK CURRENT (mA)
Sink
Sense
Figure 12. Bottom Drive Response Time versus
Current Sense Input Voltage
Figure 13. Top Drive Output Saturation Voltage
versus Sink Current
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MC33033, NCV33033
V
= 20 V
C = 1.0 nF
CC
L
100
100
T
A
= 25°C
V
= 20 V
R = 1.0 k
CC
L
C = 15 pF
0
L
0
T
A
= 25°C
50 ns/DIV
50 ns/DIV
Figure 15. Bottom Drive Output Waveform
Figure 14. Top Drive Output Waveform
0
V
CC
V
= 20 V
C = 15 pF
CC
L
−1.0
T
A
= 25°C
100
Source Saturation
(Load to Ground)
V
T
= 20 V
CC
= 25°C
−2.0
A
Sink Saturation
)
2.0
1.0
(Load to V
CC
0
Gnd
0
0
20
40
60
80
50 ns/DIV
I , OUTPUT LOAD CURRENT (mA)
O
Figure 16. Bottom Drive Output Waveform
Figure 17. Bottom Drive Output Saturation
Voltage versus Load Current
20
18
16
14
12
10
8.0
6.0
4.0
2.0
0
R = 4.7 k
T
C
= 10 nF
T
Pins 3−6, 12, 13 = Gnd
Pins 18, 19 = Open
T
A
= 25°C
0
5.0
10
15
20
25
30
V
, SUPPLY VOLTAGE (V)
CC
Figure 18. Supply Current versus Voltage
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MC33033, NCV33033
PIN FUNCTION DESCRIPTION
Pin
Symbol
Description
1, 2, 20
B , A , C
T
These three open collector Top Drive Outputs are designed to drive the external upper
power switch transistors.
T
T
3
4, 5, 6
7
Fwd//Rev
S , S , S
C
The Forward/Reverse Input is used to change the direction of motor rotation.
These three Sensor Inputs control the commutation sequence.
A
B
Reference Output
This output provides charging current for the oscillator timing capacitor C and a
T
reference for the Error Amplifier. It may also serve to furnish sensor power.
8
Oscillator
The Oscillator frequency is programmed by the values selected for the timing
components, R and C .
T
T
9
Error Amp Noninverting Input
Error Amp Inverting Input
This input is normally connected to the speed set potentiometer.
10
11
12
This input is normally connected to the Error Amp Output in open loop applications.
This pin is available for compensation in closed loop applications.
Error Amp Out/PWM Input
Current Sense Noninverting Input
A 100 mV signal, with respect to Pin 13, at this input terminates output switch
conduction during a given oscillator cycle. This pin normally connects to the top side
of the current sense resistor.
13
14
Gnd
This pin supplies a separate ground return for the control circuit and should be
referenced back to the power source ground.
V
This pin is the positive supply of the control IC. The controller is functional over a V
range of 10 to 30 V.
CC
CC
15, 16, 17
18
C , B , A
B
These three totem pole Bottom Drive Outputs are designed for direct drive of the
external bottom power switch transistors.
B
B
60°/120° Select
The electrical state of this pin configures the control circuit operation for either 60°
(high state) or 120° (low state) sensor electrical phasing inputs.
19
Output Enable
A logic high at this input causes the motor to run, while a low causes it to coast.
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MC33033, NCV33033
INTRODUCTION
The Forward/Reverse input (Pin 3) is used to change the
direction of motor rotation by reversing the voltage across
the stator winding. When the input changes state, from high
to low with a given sensor input code (for example 100), the
enabled top and bottom drive outputs with the same alpha
The MC33033 is one of a series of high performance
monolithic dc brushless motor controllers produced by
ON Semiconductor. It contains all of the functions required
to implement a limited−feature, open loop, three or four
phase motor control system. Constructed with Bipolar
Analog technology, it offers a high degree of performance
and ruggedness in hostile industrial environments. The
MC33033 contains a rotor position decoder for proper
commutation sequencing, a temperature compensated
reference capable of supplying sensor power, a frequency
programmable sawtooth oscillator, a fully accessible error
amplifier, a pulse width modulator comparator, three open
collector top drive outputs, and three high current totem pole
bottom driver outputs ideally suited for driving power
MOSFETs.
Included in the MC33033 are protective features
consisting of undervoltage lockout, cycle−by−cycle current
limiting with a latched shutdown mode, and internal thermal
shutdown.
Typical motor control functions include open loop speed
control, forward or reverse rotation, and run enable. In
addition, the MC33033 has a 60°/120° select pin which
configures the rotor position decoder for either 60° or 120°
sensor electrical phasing inputs.
designation are exchanged (A to A , B to B , C to C ).
T
B
T
B
T
B
In effect the commutation sequence is reversed and the
motor changes directional rotation.
Motor on/off control is accomplished by the Output
Enable (Pin19). When left disconnected, an internal pull−up
resistor to a positive source enables sequencing of the top
and bottom drive outputs. When grounded, the Top Drive
Outputs turn off and the bottom drives are forced low,
causing the motor to coast.
The commutation logic truth table is shown in Figure 20.
In half wave motor drive applications, the Top Drive
Outputs are not required and are typically left disconnected.
Error Amplifier
A high performance, fully compensated Error Amplifier
with access to both inputs and output (Pins 9, 10, 11) is
provided to facilitate the implementation of closed loop
motor speed control. The amplifier features a typical dc
voltage gain of 80 dB, 0.6 MHz gain bandwidth, and a wide
input common mode voltage range that extends from ground
to V . In most open loop speed control applications, the
ref
amplifier is configured as a unity gain voltage follower with
the Noninverting Input connected to the speed set voltage
source. Additional configurations are shown in Figures 30
through 34.
FUNCTIONAL DESCRIPTION
A representative internal block diagram is shown in
Figure 19, with various applications shown in Figures 35,
37, 38, 42, 44, and 45. A discussion of the features and
function of each of the internal blocks given below and
referenced to Figures 19 and 37.
Oscillator
The frequency of the internal ramp oscillator is
programmed by the values selected for timing components
R and C . Capacitor C is charged from the Reference
T
T
T
Rotor Position Decoder
Output (Pin 7) through resistor R and discharged by an
T
An internal rotor position decoder monitors the three
sensor inputs (Pins 4, 5, 6) to provide the proper sequencing
of the top and bottom drive outputs. The Sensor Inputs are
designed to interface directly with open collector type Hall
Effect switches or opto slotted couplers. Internal pull−up
resistors are included to minimize the required number of
external components. The inputs are TTL compatible, with
their thresholds typically at 2.2 V. The MC33033 series is
designed to control three phase motors and operate with four
of the most common conventions of sensor phasing. A
60°/120° Select (Pin 18) is conveniently provided which
affords the MC33033 to configure itself to control motors
having either 60°, 120°, 240° or 300° electrical sensor
phasing. With three Sensor Inputs there are eight possible
input code combinations, six of which are valid rotor
positions. The remaining two codes are invalid and are
usually caused by an open or shorted sensor line. With six
valid input codes, the decoder can resolve the motor rotor
position to within a window of 60 electrical degrees.
internal discharge transistor. The ramp peak and valley
voltages are typically 4.1 V and 1.5 V respectively. To
provide a good compromise between audible noise and
output switching efficiency, an oscillator frequency in the
range of 20 to 30 kHz is recommended. Refer to Figure 2 for
component selection.
Pulse Width Modulator
The use of pulse width modulation provides an energy
efficient method of controlling the motor speed by varying
the average voltage applied to each stator winding during the
commutation sequence. As C discharges, the oscillator sets
T
both latches, allowing conduction of the Top and Bottom
Drive Outputs. The PWM comparator resets the upper latch,
terminating the Bottom Drive Output conduction when the
positive−going ramp of C becomes greater than the Error
T
Amplifier output. The pulse width modulator timing
diagram is shown in Figure 21. Pulse width modulation for
speed control appears only at the Bottom Drive Outputs.
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MC33033, NCV33033
V
M
20 k
2
1
4
5
S
A
A
T
20 k
S
B
Sensor Inputs
20 k
Rotor
Position
Decoder
6
Top
Drive
Outputs
S
C
B
T
40 k
3
Forward/Revers
e
40 k
18
60°/120° Select
20
40 k
19
14
C
T
Output Enable
Undervoltage
Lockout
V
CC
Reference
Regulator
8.9 V
Reference Output
7
9
17
16
A
B
B
4.5 V
Noninv. Input
Faster
Error Amp
Bottom
Drive
Outputs
Thermal
Shutdown
B
10
11
PWM
R
T
Latch
R
15
Error Amp Out
PWM Input
Q
C
B
S
Latch
S
8
Oscillator
Q
C
T
I
Limit
12 Current Sense
Input
R
Sink Only
Positive True
Logic With
Hysteresis
100 mV
=
13 Gnd
Figure 19. Representative Block Diagram
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MC33033, NCV33033
Inputs (Note 2)
Sensor Electrical Phasing (Note 4)
60°
Outputs (Note 3)
Top Drives Bottom Drives
Current
Sense
120°
S
S
S
S
S
S
F/R
Enable
A
T
B
T
C
T
A
B
B
B
C
B
A
B
C
A
B
C
1
0
0
1
0
0
1
1
1
1
1
1
1
1
1
1
1
1
0
0
0
0
0
0
0
1
1
1
1
0
1
1
0
0
1
(Note 5)
F/R = 1
1
1
0
0
0
1
1
1
0
0
0
1
1
1
0
1
0
0
0
1
1
1
1
0
0
0
0
1
1
1
0
0
1
1
1
1
1
0
0
1
0
1
1
0
0
0
0
0
1
1
1
0
0
0
0
1
1
1
0
0
0
0
1
1
1
0
0
0
0
1
1
1
0
1
1
0
0
0
1
0
1
1
1
0
0
0
0
0
1
1
1
0
0
0
0
0
0
1
1
1
1
1
1
0
0
0
0
0
0
1
1
0
0
1
1
1
1
1
1
0
0
0
0
1
1
1
1
1
0
0
0
0
1
0
1
1
0
0
0
0
0
0
1
1
0
(Note 5)
F/R = 0
1
0
0
1
1
0
1
0
1
0
1
0
X
X
X
X
X
X
1
1
1
1
1
1
0
0
0
0
0
0
(Note 6)
V
V
V
V
V
V
V
V
V
V
V
V
X
X
0
1
X
1
1
1
1
1
1
1
0
0
0
0
0
0
(Note 7)
(Note 8)
NOTES: 1. V = Any one of six valid sensor or drive combinations.
X = Don’t care.
2. The digital inputs (Pins 3, 4, 5, 6, 18, 19) are all TTL compatible. The current sense input (Pin 12) has a 100 mV threshold with respect to Pin 13. A
logic 0 for this input is defined as < 85 mV, and a logic 1 is > 115 mV.
3. The top drive outputs are open collector design and active in the low (0) state.
4. With 60°/120° (Pin 18) in the high (1) state, configuration is for 60° sensor electrical phasing inputs. With Pin 18 in the low (0) state, configuration is
for 120° sensor electrical phasing inputs.
5. Valid 60° or 120° sensor combinations for corresponding valid top and bottom drive outputs.
6. Invalid sensor inputs; All top and bottom drives are off.
7. Valid sensor inputs with enable = 0; All top and bottom drives are off.
8. Valid sensor inputs with enable and current sense = 1; All top and bottom drives are off.
Figure 20. Three Phase, Six Step Commutation Truth Table (Note 1)
Current Limit
Reference
Continuous operation of a motor that is severely
over−loaded results in overheating and eventual failure.
This destructive condition can best be prevented with the use
of cycle−by−cycle current limiting. That is, each on−cycle
is treated as a separate event. Cycle−by−cycle current
limiting is accomplished by monitoring the stator current
build−up each time an output switch conducts, and upon
sensing an over current condition, immediately turning off
the switch and holding it off for the remaining duration of
oscillator ramp−up period. The stator current is converted to
The on−chip 6.25 V regulator (Pin 7) provides charging
current for the oscillator timing capacitor, a reference for the
Error Amplifier, and can supply 20 mA of current suitable
for directly powering sensors in low voltage applications. In
higher voltage applications it may become necessary to
transfer the power dissipated by the regulator off the IC. This
is easily accomplished with the addition of an external pass
transistor as shown in Figure 22. A 6.25 V reference level
was chosen to allow implementation of the simpler NPN
circuit, where V − V exceeds the minimum voltage
ref
BE
a voltage by inserting a ground−referenced sense resistor R
required by Hall Effect sensors over temperature. With
proper transistor selection, and adequate heatsinking, up to
one amp of load current can be obtained.
S
(Figure 35) in series with the three bottom switch transistors
(Q , Q , Q ). The voltage developed across the sense
4
5
6
resistor is monitored by the current sense input (Pin 12), and
compared to the internal 100 mV reference. If the current
sense threshold is exceeded, the comparator resets the lower
latch and terminates output switch conduction. The value for
the sense resistor is:
Undervoltage Lockout
A dual Undervoltage Lockout has been incorporated to
prevent damage to the IC and the external power switch
transistors. Under low power supply conditions, it
guarantees that the IC and sensors are fully functional, and
that there is sufficient Bottom Drive Output voltage. The
0.1
R
+
S
I
stator(max)
positive power supply to the IC (V ) is monitored to a
CC
threshold of 8.9 V. This level ensures sufficient gate drive
The dual−latch PWM configuration ensures that only one
single output conduction pulse occurs during any given
oscillator cycle, whether terminated by the output of the
Error Amplifier or the current limit comparator.
necessary to attain low R
when interfacing with
DS(on)
standard power MOSFET devices. When directly powering
the Hall sensors from the reference, improper sensor
http://onsemi.com
12
MC33033, NCV33033
operation can result if the reference output voltage should
fall below 4.5 V. If one or both of the comparators detects an
undervoltage condition, the top drives are turned off and the
Bottom Drive Outputs are held in a low state. Each of the
comparators contain hysteresis to prevent oscillations when
crossing their respective thresholds.
UVLO
14
7
V
in
Capacitor C
T
REF
Error Amp Out/
PWM Input
MPS
U01A
To
Current Sense
Input
Control
Circuitry
6.25 V
Sensor
Power
≈ꢁ5.6 V
Latch ꢀSet"
Inputs
UVLO
36
14
7
V
in
REF
MPS
U51A
Top Drive
Outputs
0.1
Bottom Drive
Outputs
To Control Circuitry
and Sensor Power
6.25 V
The NPN circuit is recommended for powering Hall or opto sensors,
where the output voltage temperature coefficient is not critical. The PNP
circuit is slightly more complex, but also more accurate. Neither circuit
has current limiting.
Figure 21. PWM Timing Diagram
Figure 22. Reference Output Buffers
V
M
V
= 12 V
V
V = 170 V
M
CC
Boost
2
Q
V
2
CC
2
1
1.0 k
1
A
T
Rotor
Position
Decoder
A
5
T
Q
Q
3
1
Rotor
Position
Decoder
6
1
B
T
1.0 M
4
2
B
T
20
20
4.7 k
C
T
C
T
1N4744
MOC8204
Optocoupler
Load
Load
17
16
15
17
16
15
Q
4
Transistor Q is a common base stage used to level shift from V to the high
1
CC
motor voltage, V . The collector diode is required if V is present while V
M
CC
M
is low.
Figure 23. High Voltage Interface with
NPN Power Transistors
Figure 24. High Voltage Interface with
N−Channel Power MOSFETs
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13
MC33033, NCV33033
R
g
17
16
17
16
D
R
g
D
D
R
g
15
12
15
12
R
R
C
S
100 mV
100 mV
D = 1N5819
Series gate resistor R will damp any high frequency oscillations caused
g
The addition of the RC filter will eliminate current−limit
instability caused by the leading edge spike on the current
by the MOSFET input capacitance and any series wiring induction in the
gate−source circuit. Diode D is required if the negative current into the
Bottom Drive Outputs exceeds 50 mA.
waveform. Resistor R should be a low inductance type.
S
Figure 25. Current Waveform Spike Suppression
Figure 26. MOSFET Drive Precautions
C
D
SENSEFET
17
S
17
16
G
K
M
C
16
C
15
15
12
I
B
Power Ground:
To Input Source Return
12
+
0
−
t
100 mV
R
@ I @ R
pk
100 mV
S
DS(on)
) R
S
V
[
R
Pin 9
S
ꢂr
DM(on)
Base Charge
Removal
13 Gnd
If : SENSEFET = MPT10N10M
= 200 Ω , 1/4 W
[ 0.75 I
R
S
V
Then :
9
Pin
pk
The totem pole output can furnish negative base current for
enhanced transistor turn−off, with the addition of capacitor C.
Virtually lossless current sensing can be achieved with the
implementation of SENSEFET power switches.
Figure 27. Bipolar Transistor Drive
Figure 28. Current Sensing Power MOSFETs
V
+ 12
+ 8.0
+ 4.0
M
REF
7
V
= 12 V
8
C
V
M
40 k
19
4
V
R
7
3
M
1
9
6
20
40
Boost Current (mA)
V
60
A
R
S
R
EA
2
R
1.0 μ/200 V
5
2
Q
3
10
11
*
V
B
V
Boost
PWM
R
4
22
*
1N5352A
1
MC1455
V
= 170 V
M
R ) R
R
R
4
18 k
0.001
3
4
2
ꢂ –ꢂ
* = MUR115
V
ꢂ
+ V ꢂ
ꢂ
ꢂV
ǒ Ǔ ǒ Ǔ
Pin 11
A
B
R ) R
R
R
This circuit generates V
for Figure 24.
Boost
1
2
3
3
Figure 29. High Voltage Boost Supply
Figure 30. Differential Input Speed Controller
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14
MC33033, NCV33033
5.0 V
16
11 166 k
REF
EA
V
CC
Q
9
7
10
9
100 k
145 k
126 k
108 k
92.3 k
77.6 k
63.6 k
51.3 k
Q
8
7
6
5
REF
Q
Q
Q
7
40 k
19
9
7
12
13
14
15
P3
6
5
4
P2
P1
P0
Enable
40 k
BCD
Inputs
19
9
Q
Q
4
10
11
R
1
2
PWM
3
3
2
Q2
Increase
Speed
EA
R
40.4 k
10
11
Q
1
Q
0
PWM
1
Gnd
C
8
Resistor R with capacitor C sets the acceleration time constant while R
The SN74LS145 is an open collector BCD to One of Ten decoder. When
connected as shown, input codes 0000 through 1001 steps the PWM in
increments of approximately 10% from 0 to 90% on−time. Input codes 1010
through 1111 will produce 100% on−time or full motor speed.
1
2
controls the deceleration. The values of R and R should be at least ten times
1
2
greater than the speed set potentiometer to minimize time constant variations
with different speed settings.
Figure 31. Controlled Acceleration/Deceleration
Figure 32. Digital Speed Controller
R ) R
R
R
REF
3
4
2
4
V
V
ꢂ
+ V
ꢂ
ꢂ
ꢂ –ꢂ
ꢂV
ǒ Ǔ ǒ Ǔ
11
REF
EA
Pin
ref
B
R ) R
R
R
7
1
2
3
3
7
To Sensor
Input (Pin 4)
V
ꢂ
40 k
ref
19
9
+
40 k
R
B
1
19
9
T
R
5
ꢂ)ꢂ 1
ǒ Ǔ
0.01
10 k
100 k
1.0 M
R
R
5
Increase
Speed
EA
6
10
11
R
2
R
3
10
11
10 M
PWM
10 k
R §§ R ꢂ øꢂ R
6
PWM
R
3
6
R
4
0.1
6
0.22
The rotor position sensors can be used as a tachometer. By differentiating the
positive−going edges and then integrating them over time, a voltage
proportional to speed can be generated. The error amp compares this voltage
to that of the speed set to control the PWM.
This circuit can control the speed of a cooling fan proportional to the difference
between the sensor and set temperatures. The control loop is closed as the
forced air cools the NTC thermistor. For controlled heating applications,
exchange the positions of R and R .
1
2
Figure 33. Closed Loop Speed Control
Figure 34. Closed Loop Temperature Control
Drive Outputs
SYSTEM APPLICATIONS
The three Top Drive Outputs (Pins 1, 2, 20) are open
collector NPN transistors capable of sinking 50 mA with a
minimum breakdown of 30 V. Interfacing into higher
voltage applications is easily accomplished with the circuits
shown in Figures 23 and 24.
The three totem pole Bottom Drive Outputs (Pins 15, 16,
17) are particularly suited for direct drive of N−Channel
MOSFETs or NPN bipolar transistors (Figures 25, 26, 27,
and 28). Each output is capable of sourcing and sinking up
to 100 mA.
Three Phase Motor Commutation
The three phase application shown in Figure 35 is an open
loop motor controller with full wave, six step drive. The
upper power switch transistors are Darlington PNPs while
the lower switches are N−Channel power MOSFETs. Each
of these devices contains an internal parasitic catch diode
that is used to return the stator inductive energy back to the
power supply. The outputs are capable of driving a delta or
wye connected stator, and a grounded neutral wye if split
supplies are used. At any given rotor position, only one top
and one bottom power switch (of different totem poles) is
enabled. This configuration switches both ends of the stator
winding from supply to ground which causes the current
flow to be bidirectional or full wave. A leading edge spike
is usually present on the current waveform and can cause a
current−limit error. The spike can be eliminated by adding
Thermal Shutdown
Internal thermal shutdown circuity is provided to protect
the IC in the event the maximum junction temperature is
exceeded. When activated, typically at 170°C, the IC acts as
though the regulator was disabled, in turn shutting down the
IC.
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15
MC33033, NCV33033
an RC filter in series with the Current Sense Input. Using a
to 720°) shows a reduced speed with about 50% pulse width
modulation. The current waveforms reflect a constant
torque load and are shown synchronous to the commutation
frequency for clarity.
low inductance type resistor for R will also aid in spike
S
reduction. Figure 36 shows the commutation waveforms
over two electrical cycles. The first cycle (0° to 360°) depicts
motor operation at full speed while the second cycle (360°
V
M
2
1
4
5
Q
N
N
1
S
S
A
B
Rotor
Position
Decoder
6
Q
2
3
FWR/REV
18
60°/120°
20
Q
3
19
C
Enable
Undervoltage
14
V
Motor
M
Lockout
Reference
Regulator
7
17
16
15
Q
4
Speed
Set
Error Amp
9
Q
Thermal
Shutdown
5
10
11
Faster
PWM
R
T
R
S
Q
Q
Q
6
8
Oscillator
S
R
C
T
I
R
Limit
12
R
C
S
13 Gnd
Figure 35. Three Phase, Six Step, Full Wave Motor Controller
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16
MC33033, NCV33033
Rotor Electrical Position (Degrees)
0
60
120
180
240
300
360
420
480
540
600
660
720
S
A
Sensor Inputs
60°/120°
S
B
Select Pin
S
Open
C
100
001
000
Code
100
110
111
011
001
000
110
111
011
S
A
Sensor Inputs
60°/120°
S
B
Select Pin
S
C
Grounded
Code
100
110
010
011
001
101
100
110
010
011
001
101
A
T
Top Drive
Outputs
B
T
C
T
A
B
B
Bottom Drive
Outputs
B
C
B
Conducting
Power Switch
Transistors
Q + Q Q + Q
2
Q + Q Q + Q Q + Q Q + Q Q + Q Q + Q Q + Q Q + Q Q + Q Q + Q
2 4 3 4 3 5 1 5 1 6 2 6 2 4 3 4 3 5 1
1
6
6
5
+
A
B
C
O
−
+
Motor Drive
Current
O
−
+
O
−
Full Speed (No PWM)
Reduced Speed (≈ 50% PWM)
FWD/REV = 1
Figure 36. Three Phase, Six Step, Full Wave Commutation Waveforms
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17
MC33033, NCV33033
Figure37 shows a three phase, three step, half wave motor
stator winding. Current flow is unidirectional or half wave
because only one end of each winding is switched. The stator
flyback voltage is clamped by a single zener and three
diodes.
controller. This configuration is ideally suited for
automobile and other low voltage applications since there is
only one power switch voltage drop in series with a given
Motor
2
4
5
N
S
S
N
V
M
1
Rotor
Position
Decoder
6
3
FWR/REV
18
60°/120°
20
19
Enable
Undervoltage
14
V
M
Lockout
Reference
Regulator
7
9
17
16
15
Speed
Set
Error Amp
Thermal
Shutdown
10
11
Faster
PWM
R
T
R
S
Q
Q
8
Oscillator
S
R
C
T
I
Limit
12
13
Gnd
Figure 37. Three Phase, Three Step, Half Wave Motor Controller
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18
MC33033, NCV33033
Three Phase Closed Loop Controller
The MC33033, by itself, is capable of open loop motor
speed control. For closed loop speed control, the MC33033
requires an input voltage proportional to the motor speed.
Traditionally this has been accomplished by means of a
tachometer to generate the motor speed feedback voltage.
Figure 38 shows an application whereby an MC33039,
powered from the 6.25 V reference (Pin 7) of the MC33033,
is used to generate the required feedback voltage without the
need of a costly tachometer. The same Hall sensor signals
used by the MC33033 for rotor position decoding are
utilized by the MC33039. Every positive or negative going
transition of the Hall sensor signals on any of the sensor lines
causes the MC33039 to produce an output pulse of defined
amplitude and time duration, as determined by the external
pulses present at Pin 5 of the MC33039 are integrated by the
Error Amplifier of the MC33033 configured as an
integrator, to produce a dc voltage level which is
proportional to the motor speed. This speed proportional
voltage establishes the PWM reference level at Pin 11 of the
MC33033 motor controller and completes or closes the
feedback loop. The MC33033 outputs drive a TMOS power
MOSFET 3−phase bridge. High current can be expected
during conditions of start−up and when changing direction
of the motor.
The system shown in Figure 38 is designed for a motor
having 120/240 degrees Hall sensor electrical phasing. The
system can easily be modified to accommodate 60/300
degree Hall sensor electrical phasing by removing the
resistor R and capacitor C . The resulting output train of
jumper (J ) at Pin 18 of the MC33033.
1
1
1
1
2
3
4
8
7
6
5
1.0 M
R
V
(18 to 30 V)
M
1
MC33039
750 pF
C
1
0.1
1000
1.1 k 1.1 k 330
1.1 k
TP1
1.0 k
1.0 k
20
1.0 k
N
N
1
2
Enable
4.7 k
J
S
S
19
18
17
16
15
14
13
12
11
F/R
3
470
470
470
1
4
5
MC33033
6
Motor
7
0.01
Speed
Faster
5.1 k
1N5819
8
9
100
10
1N4742
0.1
TP2
1.0 M
0.1
0.05/1.0 W
0.1
33
10 k
100 k
Close Loop
Figure 38. Closed Loop Brushless DC Motor Control With the MC33033 Using the MC33039
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19
MC33033, NCV33033
Sensor Phasing Comparison
There are four conventions used to establish the relative
phasing of the sensor signals in three phase motors. With six
step drive, an input signal change must occur every 60
electrical degrees, however, the relative signal phasing is
dependent upon the mechanical sensor placement. A
comparison of the conventions in electrical degrees is shown
in Figure 39. From the sensor phasing table (Figure 40), note
that the order of input codes for 60° phasing is the reverse of
300°. This means the MC33033, when the 60°/120° select
(Pin 18) and the FWD/REV (Pin 3) both in the high state
(open), is configured to operate a 60° sensor phasing motor
in the forward direction. Under the same conditions a 300°
sensor phasing motor would operate equally well but in the
reverse direction. One would simply have to reverse the
FWD/REV switch (FWD/REV closed) in order to cause the
300° motor to also operate in the same direction. The same
difference exists between the 120° and 240° conventions.
In this data sheet, the rotor position has always been given
in electrical degrees since the mechanical position is a
function of the number of rotating magnetic poles. The
relationship between the electrical and mechanical position
is:
#Rotor Poles
Electrical Degrees + Mechanical Degreesǒ
Ǔ
2
An increase in the number of magnetic poles causes more
electrical revolutions for a given mechanical revolution.
General purpose three phase motors typically contain a four
pole rotor which yields two electrical revolutions for one
mechanical.
Two and Four Phase Motor Commutation
The MC33033 configured for 60° sensor inputs is capable
of providing a four step output that can be used to drive two
or four phase motors. The truth table in Figure 41 shows that
by connecting sensor inputs S and S together, it is possible
B
C
Rotor Electrical Position (Degrees)
to truncate the number of drive output states from six to four.
The output power switches are connected to B , C , B , and
0
60 120 180 240 300 360 420 480 540 600 660 720
T
T
B
C . Figure 42 shows a four phase, four step, full wave motor
B
S
A
control application. Power switch transistors Q through Q
1
8
60°
are Darlington type, each with an internal parasitic catch
diode. With four step drive, only two rotor position sensors
spaced at 90 electrical degrees are required. The
commutation waveforms are shown in Figure 43.
Figure 44 shows a four phase, four step, half wave motor
controller. It has the same features as the circuit in Figure 37,
except for the deletion of speed adjust.
S
S
B
C
S
A
S
B
S
C
120°
S
S
S
A
B
C
240°
300°
MC33033 (60°/120° Select Pin Open)
Inputs
Outputs
Top Drives Bottom Drives
S
A
S
B
S
C
Sensor Electrical
Spacing* = 90°
S
S
F/R
B
T
C
T
B
C
B
A
B
B
1
0
1
1
1
1
1
1
0
1
1
0
0
1
1
0
0
1
1
1
0
1
0
0
1
0
0
0
Figure 39. Sensor Phasing Comparison
Sensor Electrical Phasing (Degrees)
1
1
0
0
0
1
1
0
0
0
0
0
1
1
1
0
0
1
1
1
0
1
0
0
0
0
1
0
60°
120°
240°
300°
*With MC33033 sensor input S connected to S
S
S
S
S
S
S
S
S
S
S
S
S
C
B
C
A
B
C
A
B
C
A
B
C
A
B
1
0
0
1
0
0
1
1
1
0
1
1
1
0
0
0
1
1
0
1
1
1
0
0
0
1
1
Figure 41. Two and Four Phase, Four Step,
Commutation Truth Table
1
1
0
0
0
1
1
1
0
0
0
1
1
1
0
1
1
0
0
0
0
0
0
1
1
1
1
0
0
0
0
1
1
1
0
1
1
0
0
0
0
0
0
1
1
Figure 40. Sensor Phasing Table
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20
MC33033, NCV33033
Figure 42. Four Phase, Four Step, Full Wave Controller
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21
MC33033, NCV33033
Rotor Electrical Position (Degrees)
0
90
180
270
360
450
540
630
720
S
S
A
Sensor Inputs
60°/120°
B
Select Pin
Open
Code
10
10
01
00
10
11
01
00
B
T
Top Drive
Outputs
C
T
B
B
Bottom Drive
Outputs
C
B
Conducting
Power Switch
Transistors
Q + Q
3
Q + Q
4
Q + Q
1
Q + Q
2
Q + Q
3
Q + Q
4
Q + Q
1
Q + Q
2 8
5
6
7
8
5
6
7
+
A
B
C
D
O
−
+
O
−
Motor Drive
Current
+
O
−
+
O
−
Full Speed (No PWM)
FWD/REV = 1
Figure 43. Four Phase, Four Step, Full Wave Commutation Waveforms
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22
MC33033, NCV33033
Figure 44. Four Phase, Four Step, Half Wave Motor Controller
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23
MC33033, NCV33033
Brush Motor Control
Though the MC33033 was designed to control brushless dc
motors, it may also be used to control dc brush−type motors.
Figure 45 shows an application of the MC33033 driving a
H−bridge affording minimal parts count to operate a
brush−type motor. Key to the operation is the input sensor
fly, using the normal Forward/Reverse switch, and not have
to completely stop before reversing.
LAYOUT CONSIDERATIONS
Do not attempt to construct any of the motor control
circuits on wire−wrap or plug−in prototype boards. High
frequency printed circuit layout techniques are imperative to
prevent pulse jitter. This is usually caused by excessive noise
pick−up imposed on the current sense or error amp inputs.
The printed circuit layout should contain a ground plane
with low current signal and high drive and output buffer
grounds returning on separate paths back to the power
code [100] which produces a top−left (Q ) and a bottom−right
1
(Q ) drive when the controller’s Forward/Reverse pin is at
3
logic [1]; top−right (Q ), bottom−left (Q ) drive is realized
4
2
when the Forward/Reverse pin is at logic [0]. This code
supports the requirements necessary for H−bridge drive
accomplishing both direction and speed control.
The controller functions in a normal manner with a pulse
width modulated frequency of approximately 25 kHz.
Motor speed is controlled by adjusting the voltage presented
to the noninverting input of the Error Amplifier establishing
the PWM′s slice or reference level. Cycle−by−cycle current
limiting of the motor current is accomplished by sensing the
supply input filter capacitor V . Ceramic bypass capacitors
M
(0.01 μF) connected close to the integrated circuit at V
ref
,
CC
V
and error amplifier noninverting input may be required
depending upon circuit layout. This provides a low
impedance path for filtering any high frequency noise. All
high current loops should be kept as short as possible using
heavy copper runs to minimize radiated EMI.
voltage (100 mV threshold) across the R resistor to ground
S
of the H−bridge motor current. The over current sense circuit
makes it possible to reverse the direction of the motor, on the
+12 V
2
4
5
1.0 k
Rotor
Position
Decoder
6
1
Q *
1
1.0 k
3
FWR/REV
18
20
Q *
4
19
14
Enable
+12 V
Undervoltage
Lockout
0.1
DC Brush
M
Reference
Regulator
Motor
Q *
2
7
9
17
16
15
22
Error Amp
10 k
Thermal
Shutdown
10
11
Faster
PWM
10 k
R
S
Q *
3
Q
Q
22
8
Oscillator
S
R
0.005
I
1.0 k
Limit
12
0.001
R
S
13 Gnd
Figure 45. H−Bridge Brush−Type Controller
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24
MC33033, NCV33033
ORDERING INFORMATION
†
Device
MC33033DW
Operating Temperature Range
Package
Shipping
SO−20L
38 Units / Rail
1000 Tape & Reel
18 Units / Rail
MC33033DWG
SO−20L
(Pb−Free)
MC33033DWR2
SO−20L
T = −40°C to +85°C
A
MC33033DWR2G
SO−20L
(Pb−Free)
MC33033P
PDIP−20
MC33033PG
PDIP−20
(Pb−Free)
NCV33033DWR2*
NCV33033DWR2G*
SO−20L
1000 Tape & Reel
T = −40°C to +125°C
A
SO−20L
(Pb−Free)
†For information on tape and reel specifications, including part orientation and tape sizes, please refer to our Tape and Reel Packaging
Specification Brochure, BRD8011/D.
*NCV33033: T = −40C, T
= +125C. Guaranteed by design. NCV prefix is for automotive and other applications requiring site and change
low
high
control.
MARKING DIAGRAMS
SO−20L
DW SUFFIX
CASE 751D
PDIP−20
P SUFFIX
CASE 738
20
20
MC33033DW
AWLYYWWG
MC33033P
AWLYYWWG
1
1
20
20
NCV33033DW
AWLYYWWG
NCV33033P
AWLYYWWG
1
1
A
= Assembly Location
= Wafer Lot
= Year
= Work Week
= Pb−Free Package
WL
YY
WW
G
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25
MC33033, NCV33033
PACKAGE DIMENSIONS
PDIP−20
P SUFFIX
CASE 738−03
ISSUE E
−A−
NOTES:
1. DIMENSIONING AND TOLERANCING PER ANSI
Y14.5M, 1982.
2. CONTROLLING DIMENSION: INCH.
3. DIMENSION L TO CENTER OF LEAD WHEN
FORMED PARALLEL.
20
1
11
10
B
4. DIMENSION B DOES NOT INCLUDE MOLD
FLASH.
C
L
INCHES
MIN MAX
1.010 1.070 25.66 27.17
MILLIMETERS
DIM
A
B
C
D
E
MIN MAX
0.240 0.260
0.150 0.180
0.015 0.022
6.10
3.81
0.39
6.60
4.57
0.55
−T−
SEATING
PLANE
K
M
0.050 BSC
0.050 0.070
1.27 BSC
1.27
1.77
F
E
N
G
J
0.100 BSC
0.008 0.015
0.110 0.140
0.300 BSC
2.54 BSC
0.21
2.80
0.38
3.55
G
F
J 20 PL
K
L
7.62 BSC
D 20 PL
M
M
0.25 (0.010)
T B
0°
0.020 0.040
15°
0°
0.51
15°
1.01
M
N
M
M
T A
0.25 (0.010)
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26
MC33033, NCV33033
PACKAGE DIMENSIONS
SO−20L
DW SUFFIX
CASE 751D−05
ISSUE G
D
A
q
NOTES:
1. DIMENSIONS ARE IN MILLIMETERS.
2. INTERPRET DIMENSIONS AND TOLERANCES
PER ASME Y14.5M, 1994.
20
11
3. DIMENSIONS D AND E DO NOT INCLUDE MOLD
PROTRUSION.
E
B
4. MAXIMUM MOLD PROTRUSION 0.15 PER SIDE.
5. DIMENSION B DOES NOT INCLUDE DAMBAR
PROTRUSION. ALLOWABLE PROTRUSION SHALL
BE 0.13 TOTAL IN EXCESS OF B DIMENSION AT
MAXIMUM MATERIAL CONDITION.
1
10
MILLIMETERS
DIM MIN
MAX
2.65
0.25
0.49
0.32
12.95
7.60
20X B
A
A1
B
C
D
E
2.35
0.10
0.35
0.23
12.65
7.40
M
S
S
B
0.25
T A
e
1.27 BSC
A
H
h
10.05
0.25
0.50
0
10.55
0.75
0.90
7
L
SEATING
PLANE
q
_
_
18X e
A1
C
T
ON Semiconductor and
are registered trademarks of Semiconductor Components Industries, LLC (SCILLC). SCILLC reserves the right to make changes without further notice
to any products herein. SCILLC makes no warranty, representation or guarantee regarding the suitability of its products for any particular purpose, nor does SCILLC assume any liability
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MC33033/D
相关型号：
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