SC284PEVB [SEMTECH]
Dual Channel 2.5MHz, 2.0A Synchronous Buck with Automatic Power Save;型号: | SC284PEVB |
厂家: | SEMTECH CORPORATION |
描述: | Dual Channel 2.5MHz, 2.0A Synchronous Buck with Automatic Power Save |
文件: | 总22页 (文件大小:2696K) |
中文: | 中文翻译 | 下载: | 下载PDF数据表文档文件 |
SC284P
Dual Channel 2.5MHz, 2.0A Synchronous
Buck with Automatic Power Save
POWER MANAGEMENT
Features
Description
VIN Range — 2.75 – 5.5V
The SC284P is a dual channel 2A synchronous step-down
regulator designed to operate with an input voltage
range of 2.75 to 5.5 Volts. Each channel offers seven
pre-determined output voltages via three control pins
programmable from ꢀ.0 to 3.3 Volts. The control pins
allow for on-the-fly voltage changes, enabling system
designers to implement dynamic power savings. The
SC284P is also capable of adjusting the output voltage
via an external resistor divider.
VOUT Selectable — ꢀ.0 - 3.3V
Up to 2A Output Current for Each Channel
Package with Ultra-Small Footprint : 3 x 3 x 0.6(mm)
Switching Frequency — 2.5MHz
Efficiency Up to 94%
High Light-load Efficiency via Automatic PSAVE
Mode
Low Output Noise in CCM
The SC284P is optimized for maximum efficiency over a
wide range of load currents. During full load operation,
the device operates in PWM mode with fixed 2.5MHz
oscillator frequency, allowing the use of small surface
mount external components. As the load decreases,
the regulator will transition into Power Save mode
maintaining high efficiency.
Excellent Transient Response
Start Up into Pre-Biased Output
ꢀ00% Duty-Cycle Low Dropout Operation
Shutdown Current — <ꢀµA
Internal Soft-Start
Input Under-Voltage Lockout
Output Over-Voltage, Current Limit Protection
Over-Temperature Protection
VOUT Further Adjustable Using External Resistors
Connecting CTL0 — CTL2 to logic low forces the device
into shutdown mode reducing the supply current to less
than ꢀµA. Connecting any of the control pins to logic
high enables the converter and sets the output voltage
according to Table ꢀ. Other features include under-
voltage lockout, soft-start to limit inrush current, and
over-temperature protection.
PGOOD Feature
Lead-free, Halogen-free, and RoHS/WEEE Compliant
Applications
Wireless Access Point/Router/Modem
Femtocell
Set-Top Box
Point-Of-Sale
Projector
Typical Application Circuit
LA 2.2µH
PVINA
VINA
VOUTA
LXA
VOUTA
RAVINA 1Ω
COUTA
22µF
CINA
10µF
AVINA
LB 2.2µH
CAVINA 10nF
VOUTB
LXB
VOUTB
AGNDA
COUTB
22µF
SC284P
PVINB
AVINB
VINB
RAVINB 1Ω
PGNDA
CINB
10µF
CAVINB 10nF
PGNDB
CTL0B
AGNDB
CTL0A
CTL0A
CTL1A
CTL2A
CTL0B
CTL1B
CTL1A
CTL2A
CTL1B
CTL2B
CTL2B
PGOODA
PGOODB
PGOODA
PGOODB
Revision 2.ꢀ
ꢀ
© 20ꢀ4 Semtech Corporation
SC284P
Pin Configuration
Ordering Information
Device
Package
SC284PULTRC(ꢀ)(2)
SC284PEVB
3 x 3 x 0.6(mm) MLPQ-UT20
Evaluation Board
20 19
18
17
16
Notes:
(ꢀ) Available in tape and reel only. A reel contains 3,000 devices.
(2) Available in lead-free package only. Device is fully WEEE and RoHS
compliant and halogen-free.
1
2
3
15
14
13
12
11
PVINA
AGNDA
AVINA
CTL0B
PGOODB
AVINB
TOP VIEW
AGNDB
PVINB
PGOODA
CTL0A
4
5
T
6
7
8
9
10
Table 1 – Output Voltage Settings
3 x 3 x 0.6(mm) MLPQ-UT20
θJA= 40°C/W
CTL2[A/B] CTL1[A/B] CTL0[A/B]
Output Voltage
Disabled
ꢀ.0V
0
0
0
0
ꢀ
0
0
ꢀ
ꢀ
0
0
ꢀ
0
ꢀ
0
ꢀ.ꢀV
Marking Information
ꢀ.2V
ꢀ.5V
ꢀ
ꢀ
ꢀ
0
ꢀ
ꢀ
ꢀ
0
ꢀ
ꢀ.8V
2.5V
3.3V
284P = Part Number Code
yyww = Date Code
xxxx = Semtech Lot Number
2
SC284P
Absolute Maximum Ratings
Recommended Operating Conditions
AVINA, AVINB, PVINA, PVINBSupply (V) . . . . . -0.3 to +6.0
LXA and LXB (V) . . . . . . . . . -ꢀ toVIN +ꢀ, -3 (20ns Max), 6 Max
VOUTA and VOUTB (V) . . . . . . . . . . . . . . . . . . -0.3 to (VIN +0.3)
CTLXA/Bpins (V) . . . . . . . . . . . . . . . . . . . -0.3 to (VIN + 0.3)
Peak IR Reflow Temperature (°C) . . . . . . . . . . . . . . . . . . . . . 260
ESD Protection Level(2) (kV) . . . . . . . . . . . . . . . . . . . . . . . . . 3kV
Output Short Circuit to GND. . . . . . . . . . . . . . . .Continuous
VINA and VINB Supply (V) . . . . . . . . . . . . . . . . . . . . . . . 2.75 to 5.5
Maximum Output Current Each Channel (A) . . . . . . . . . 2.0
Thermal Information
Thermal Resistance, Junction to Ambient (ꢀ) (°C/W) . . . . 40
Maximum Junction Temperature (°C) . . . . . . . . . . . . . . +ꢀ50
Storage Temperature Range(°C) . . . . . . . . . . . . . . -65to+ꢀ50
Exceeding the absolute maximum ratings may result in permanent damage to the device and/or device malfunction. Operation outside of the
parameters specified in the Electrical Characteristics section is not recommended.
Notes:
(ꢀ) Calculated from package in still air, mounted to 3 x 4.5 (in), 4 layer FR4 PCB with thermal vias under the exposed pad per JESD5ꢀ standards.
(2) Tested according to JEDEC standard JESD22-Aꢀꢀ4-B.
Electrical Characteristics
Unless specified: VINA= VINB= 5.0V, VOUTA= VOUTB= ꢀ.5V, CINA= CINB=ꢀ0µF, COUTA=COUTB= 22µF, L= 2.2µH, -40°C ≤ (TA = TJ )≤ +ꢀ25 °C. Unless otherwise
noted typical values are TA= +25 °C.
Parameter
Symbol
Conditions
Min
2.75
2.55
Typ
Max Units
Input Voltage Range
VINA/B
5.5
V
V
2.65
200
2.75
Rising VINA ,VINB
Hysteresis
Under-Voltage Lockout
Quiescent Current
UVLO
IQ
mV
Channel A & B, PWM mode excluding IOUT
,
6
mA
per channel
60
ꢀ
µA
µA
µs
V
IOUT = 0mA, CTLX = VIN
CTL0-2= GND, Per channel
Shutdown Current
Soft-Start Time
ISHDN
tSS
ꢀ0
Channel A & B; IOUT= 2A, VOUT =90% of final value
ꢀ700
Output Voltage Range
VOUT
ꢀ.0
3.3
Channel A & B; IOUT=400mA, PWM Mode
PSAVE Mode
-2.0
+2.0
Output Voltage Tolerance(ꢀ)
CTL Settings Regulation
ΔVOUT
%
%
ꢀ.75
ꢀ
Channel A & B; Relative to VOUT at CTL=ꢀ00,
IOUTA=400mA; IOUTB=400mA; PWM Mode
ΔVCTL-REG
Line Regulation
Load Regulation
ΔVLINE-REG
ΔVLOAD-REG
Channel A & B; VIN= 2.75 – 5.5V; PWM Mode
Channel A & B; VIN = 5.0V; IOUT=ꢀmA – 2A
0.2
0.3
%/V
%/A
3
SC284P
Electrical Characteristics (continued)
Parameter
Symbol
Conditions
Channel A & B; Peak LX current
Channel A & B
Min
2.25
2.0
Typ
3.0
2.5
-ꢀ
Max Units
Current Limit Threshold
Oscillator Frequency
ILIMIT
3.75
3.0
A
fOSC
MHz
Channel A & B; VIN = 5.5V; LX = 0V; CTL0-2= GND
Channel A & B; VIN = 5.5V; LX= 5.0V; CTL0-2= GND
Average LX Current, VOUT =ꢀ.5V
Channel A & B; ILX= ꢀ00mA, TJ= 25 °C
Channel A & B; ILX= -ꢀ00mA, TJ= 25 °C
Channel A & B; CTL0-2=VIN or GND
Channel A & B
-ꢀ0
LX Leakage Current(2)
ILK(LX)
µA
mA
mΩ
ꢀ
ꢀ0
Foldback Holding Current
High Side Switch Resistance(3)
Low Side Switch Resistance
CTLx Input Current(2)
ICL_HOLD
RDSON_P
RDSON_N
ICTL_
600
95
65
-2.0
ꢀ.6
2.0
0.4
µA
V
CTLx Input High Threshold
CTLx Input Low Threshold
Impedence of PGOOD Low
PGOOD Threshold
VCTLx_HI
VCTLx_LO
RPGOOD_LO
VPG_TH
Channel A & B
V
8
90
2
Ω
VOUT rising
Asserted
%
ms
μs
%
°C
°C
PGOOD Delay
VPG_DLY
PGOOD= Low
Channel A & B
Channel A & B
Channel A & B
20
ꢀꢀ5
ꢀ60
ꢀ0
VOUT Over Voltage Protection
VOVP
TSD
Thermal Shutdown Temperature(4)
Thermal Shutdown Hysteresis(4)
TSD_HYS
Notes:
(ꢀ) The “Output Voltage Tolerance”includes output voltage accuracy, voltage drift over temperature.
(2) A negative current means the current flows from the pin and a positive current means the current flows into the pin.
(3) Measured from VINA/B to LXA/B
(4) Thermal shutdown protection is independent for each channel.
.
4
SC284P
Typical Characteristics
Circuit Conditions: CIN= ꢀ0uF/6.3V; COUT= 22uF/6.3V, Unless otherwise noted, L= 2.2uH (TOKO: ꢀꢀ27AS-2R2M).
Efficiency vs. Load Current
Total Loss (Per Channel) vs. Load Current
100
90
80
70
60
50
1000
800
600
400
200
0
TA=25℃
VIN = 5V, VOUT = 3.3V
Vin=3.3V,Vo=1.5V
VIN = 3.3V, VOUT = 1.5V
VIN = 5V, VOUT = 1.5V
Vin=5V,Vo=3.3V
Vin=5V,Vo=1.5V
0
0.5
1.0
1.5
2.0
0.001
0.01
0.1
1
10
Load Current (A)
Load Current (A)
Steady State (PSAVE) Operation (IOUT=200mA)
Steady State (PWM) Operation (IOUT=2A)
IOUT
2A/div
IOUT
200mA/div
ILX
ILX
500mA/div
ꢀA/div
VLX
VLX
2V/div
2V/div
VIN = 5V
500ns/div
500ns/div
VIN = 5V
VOUT = ꢀ.5V
VOUT = ꢀ.5V
UVLO Hysteresis
UVLO Rising Threshold
2.70
2.68
2.66
2.64
2.62
2.60
200
195
190
185
180
175
170
-50
-25
0
25
50
75
100
125
150
-50
-25
0
25
50
75
100
125
150
Ambient Temperature (0C)
Ambient Temperature (0C)
5
SC284P
Typical Characteristics
Circuit Conditions: CIN= ꢀ0uF/6.3V; COUT= 22uF/6.3V, Unless otherwise noted, L= 2.2uH (TOKO: ꢀꢀ27AS-2R2M).
Load Regulation, Vout=1.0V
Load Regulation, Vout=1.2V
1.27
1.25
1.22
1.20
1.17
1.15
1.12
1.10
1.05
1.00
0.95
0.90
1250C
1250C
250C
250C
-400C
-400C
0.0
0.5
1.0
1.5
2.0
0.0
0.5
1.0
1.5
2.0
Load Current (A)
Load Current (A)
Load Regulation, Vout=1.8V
Load Regulation, Vout=1.5V
1.60
1.90
1.85
1.80
1.75
1.70
1.55
1.50
1.45
1.40
1250C
1250C
250C
250C
-400C
-400C
0.0
0.5
1.0
1.5
2.0
0.0
0.5
1.0
1.5
2.0
Load Current (A)
Load Current (A)
Load Regulation, Vout=2.5V
Load Regulation, Vout=3.3V
3.45
3.40
3.35
3.30
3.25
3.20
3.15
2.65
2.60
2.55
2.50
2.45
2.40
2.35
1250C
1250C
250C
-400C
250C
-400C
0.0
0.5
1.0
1.5
2.0
0.0
0.5
1.0
1.5
2.0
Load Current (A)
Load Current (A)
6
SC284P
Typical Characteristics
Circuit Conditions: CIN= ꢀ0uF/6.3V; COUT= 22uF/6.3V, Unless otherwise noted, L= 2.2uH (TOKO: ꢀꢀ27AS-2R2M).
Line Regulation, Vout=1.0V, Iout=500mA
1.05
Line Regulation, Vout=1.2V, Iout=500mA
1.26
1.24
1.22
1.20
1.18
1.16
1.14
1.04
1.03
1.02
1250C
1250C
250C
1.01
250C
1.00
-400C
-400C
0.99
0.98
0.97
0.96
0.95
2.5
3.0
3.5
4.0
4.5
5.0
5.5
2.5
3.0
3.5
4.0
4.5
5.0
5.5
Input Voltage (V)
Inout Voltage (V)
Line Regulation, Vout=1.8V, Iout=500mA
Line Regulation, Vout=1.5V, Iout=500mA
1.58
1.89
1.87
1.85
1.83
1.81
1.79
1.77
1.75
1.73
1.71
1.56
1.54
1.52
1.50
1.48
1.46
1.44
1250C
250C
1250C
250C
-400C
-400C
2.5
3.0
3.5
4.0
4.5
5.0
5.5
2.5
3.0
3.5
4.0
4.5
5.0
5.5
Input Voltage (V)
Input Voltage (V)
Line Regulation, Vout=2.5V, Iout=500mA
Line Regulation, Vout=3.3V, Iout = 500mA
3.46
2.62
3.42
3.38
3.34
3.30
3.26
3.22
3.18
3.14
2.58
2.54
2.50
2.46
2.42
2.38
1250C
1250C
250C
-400C
250C
-400C
2.5
3.0
3.5
4.0
4.5
5.0
5.5
2.5
3.0
3.5
4.0
4.5
5.0
5.5
Input Voltage (V)
Input Voltage (V)
7
SC284P
Typical Waveforms
Circuit Conditions: CIN= ꢀ0uF/6.3V; COUT= 22uF/6.3V, L= 2.2uH (TOKO: ꢀꢀ27AS-2R2M).
Start Up (Enable) (VOUT=1.5V)
Start Up (Power up VIN=VCTLx) (VOUT=1.5V)
VIN
5V/div
VIN
2V/div
VCTL
2V/div
VOUT
ꢀV/div
VOUT
ꢀV/div
VIN = 5V
IOUT = 0.4A to 2A
50us/div
VIN = 5V
IOUT = 0.4A to 2A
50us/div
Start Up (Enable) (VOUT=3.3V)
Start Up (Power up VIN=VCTLx) (VOUT=3.3V)
VIN
5V/div
VIN
2V/div
VCTL
2V/div
VOUT
ꢀV/div
VOUT
ꢀV/div
VIN = 5V
IOUT = 2A
200us/div
VIN = 5V
IOUT = 2A
200us/div
Shutdown (Disable)(VOUT=1.5V)
Shutdown (Disable)(VOUT=3.3V)
VIN
5V/div
VIN
5V/div
VCTL
2V/div
VOUT
VCTL
2V/div
ꢀV/div
VOUT
ꢀV/div
VIN = 5V
ROUT = ꢀ.65Ω(2A)
50us/div
8
SC284P
Typical Characteristics
Circuit Conditions: CIN= ꢀ0uF/6.3V; COUT= 22uF/6.3V, Unless otherwise noted, L= 2.2uH (TOKO: ꢀꢀ27AS-2R2M).
Switching Frequency Vs Temperature, Vout=1.0V
Switching Frequency Vs Temperature, Vout=1.2V
2.575
2.575
2.57
2.565
2.56
2.57
2.565
2.56
2.555
2.55
2.555
2.55
2.545
2.54
2.545
2.54
2.535
2.535
-40
-15
10
35
60
85
110
135
-40
-15
10
35
60
85
110
135
Ambient Temperature (0C)
Ambient Temperature (0C)
Switching Frequency Vs Temperature, Vout=1.8V
Switching Frequency Vs Temperature, Vout=1.5V
2.575
2.575
2.57
2.565
2.56
2.57
2.565
2.56
2.555
2.55
2.555
2.55
2.545
2.54
2.545
2.54
2.535
2.535
-40
-15
10
35
60
85
110
135
-40
-15
10
35
60
85
110
135
Ambient Temperature (0C)
Ambient Temperature (0C)
Switching Frequency Vs Temperature, Vout=2.5V
2.575
Switching Frequency vs Temperature, Vout=3.3V
2.575
2.57
2.565
2.56
2.57
2.565
2.56
2.555
2.55
2.555
2.55
2.545
2.54
2.545
2.54
2.535
2.535
-40
-15
10
35
60
85
110
135
-40
-15
10
35
60
85
110
135
Ambient Temperature (0C)
Ambient Temperature (0C)
9
SC284P
Typical Characteristics
Circuit Conditions: CIN= ꢀ0uF/6.3V; COUT= 22uF/6.3V, Unless otherwise noted, L= 2.2uH (TOKO: ꢀꢀ27AS-2R2M).
Switching Frequency Vs Input Voltage, Vout=1.0V
Switching Frequency Vs Input Voltage, Vout=1.2V
2.65
2.65
2.6
2.55
2.5
2.6
2.55
2.5
2.45
2.45
2.5
3
3.5
4
4.5
5
5.5
2.5
3
3.5
4
4.5
5
5.5
Input Voltage (V)
Input Voltage (V)
Switching Frequency Vs Input Voltage, Vout=1.8V
Switching Frequency Vs Input Voltage, Vout=1.5V
2.65
2.65
2.6
2.55
2.5
2.6
2.55
2.5
2.45
2.45
2.5
3
3.5
4
4.5
5
5.5
2.5
3
3.5
4
4.5
5
5.5
Input Voltage (V)
Input Voltage (V)
Switching Frequency Vs Input Voltage, Vout=2.5V
2.65
Switching Frequency vs Input Voltage, Vout=3.3V
2.65
2.6
2.55
2.5
2.6
2.55
2.5
2.45
2.45
2.5
3
3.5
4
4.5
5
5.5
2.5
3
3.5
4
4.5
5
5.5
Input Voltage (V)
Input Voltage (V)
ꢀ0
SC284P
Typical Waveforms
Circuit Conditions: CIN= ꢀ0uF/6.3V; COUT= 22uF/6.3V, L= 2.2uH (TOKO: ꢀꢀ27AS-2R2M).
Transient Response (Vout=1.5V, Iout=0.1A to 0.4A)
Transient Response (Vout=1.5V, Iout=0.4A to 2A)
VOUT
VOUT
ꢀ00mV/div
50mV/div
ILX
ILX
ꢀA/div
200mA/div
IOUT
200mA/div
IOUT
ꢀA/div
VIN = 5V
IOUT = 0.4A to 2A
VIN = 5V
IOUT = 0.ꢀA to 0.4A
20us/div
20us/div
Transient Response (Vout=1.5V, Iout=0.01A to 0.1A)
Transient Response (Vout=3.3V, Iout=0.4A to 2A)
VOUT
50mV/div
VOUT
ꢀ00mV/div
ILX
ꢀA/div
ILX
500mA/div
IOUT
50mA/div
IOUT
200mA/div
VIN = 5V
IOUT = 2A
200us/div
VIN = 5V
IOUT = 2A
200us/div
Output Hard Short (VOUT=1.5V)
Output Voltage Ripple (VOUT=1.5V)
VOUT
ꢀV/div
VOUT
20mV/div
ILX
ꢀA/div
VIN = 5V
IOUT = 500mA
ꢀus/div
VIN = 5V
IOUT = 500mA
50us/div
ꢀꢀ
SC284P
Pin Descriptions
Pin #
Pin Name Pin Function
ꢀ
2
3
PVINA
AGNDA
AVINA
Channel A — Input supply voltage for the converter power stage and internal circuitry.
Ground connection for internal circuitry — connect directly to PGNDA.
Power supply for internal circuitry — must be connected to PVINA using an R-C filter of ꢀΩ and ꢀ0nF.
Power Good indicator for channel A. When the output voltage reaches the PGOODA threshold, this pin will be
open drain (after the PGOOD delay), otherwise it is pulled low internally.
4
5
PGOODA
CTL0A
Channel A — Control bit 0, see Table ꢀ for decoding. This pin has a ꢀ MΩ internal pull-down resistor. This resis-
tor is switched in circuit whenever the pin voltage is below the input high threshold, or when the part is in
under-voltage lockout.
Channel A — Control bit ꢀ, see Table ꢀ for decoding. This pin has a ꢀ MΩ internal pull-down resistor. This resis-
tor is switched in circuit whenever the pin voltage is below the input high threshold, or when the part is in
under-voltage lockout.
6
7
CTLꢀA
CTL2A
Channel A — Control bit 2, see Table ꢀ for decoding. This pin has a ꢀ MΩ internal pull-down resistor. This resis-
tor is switched in circuit whenever the pin voltage is below the input high threshold, or when the part is in
under-voltage lockout.
8
VOUTB
PGNDB
LXB
Output voltage sense pin of Channel B
9
Channel B — Ground connection for converter power stage and internal circuitry.
Switching node of Channel B — connect an inductor between this pin and the output capacitor.
Channel B — Input supply voltage for the converter power stage and internal circuitry.
Ground connection for internal circuitry — connect directly to PGNDB.
ꢀ0
ꢀꢀ
ꢀ2
ꢀ3
PVINB
AGNDB
AVINB
Power supply for internal circuitry — must be connected to PVINB using an R-C filter of ꢀΩ and ꢀ0nF.
Power Good indicator for channel B. When the output voltage reaches the PGOODB threshold, this pin will be
open drain (after the PGOOD delay), otherwise it is pulled low internally.
ꢀ4
ꢀ5
PGOODB
CTL0B
Channel B — Control bit 0, see Table ꢀ for decoding. This pin has a ꢀ MΩ internal pulld-own resistor. This resis-
tor is switched in circuit whenever the pin voltage is below the input high threshold, or when the part is in
under-voltage lockout.
Channel B — Control bit ꢀ - see Table ꢀ for decoding. This pin has a ꢀ MΩ internal pull-down resistor. This
resistor is switched in circuit whenever the pin voltage is below the input high threshold, or when the part is
in under-voltage lockout.
ꢀ6
ꢀ7
CTLꢀB
CTL2B
Channel B — Control bit 2, see Table ꢀ for decoding. This pin has a ꢀ MΩ internal pull-down resistor. This resis-
tor is switched in circuit whenever the pin voltage is below the input high threshold, or when the part is in
under-voltage lockout.
ꢀ8
ꢀ9
20
VOUTA
PGNDA
LXA
Output voltage sense pin of Channel A
Channel A — Ground connection for converter power stage and internal circuitry.
Switching node of Channel A — connect an inductor between this pin and the output capacitor.
Thermal pad for heatsinking purposes.
PAD
ꢀ2
SC284P
Block Diagram
1
PVINA
Current Amp
AVINA
3
Plimit Amp
Oscillator and
Slope Generator
Control
Logic
20
LXA
18
VOUTA
CTL0A
CTL1A
CTL2A
PWM
Comp
Error Amp
5
6
7
500mV
Ref
Voltage
Select
19
PGNDA
PSAVE
Comp
2
AGNDA
PGOOD
Detector
Delay
4
PGOODA
AVINB
11
PVINB
Current Amp
13
Plimit Amp
Oscillator and
Slope Generator
Control
Logic
10
LXB
8
VOUTB
CTL0B
PWM
Comp
15
Error Amp
500mV
Ref
Voltage
Select
CTL1B 16
9
PGNDB
17
12
CTL2B
PSAVE
Comp
AGNDB
PGOOD
Detector
Delay
PGOODB
14
ꢀ3
SC284P
Applications Information
enough in value for the current through the resistor chain
to be at least 20µA in order to ignore the VOUT pin current.
Detailed Description
The SC284P is a two channel synchronous step-down
converter. Both channels of this device are designed
to operate at a fixed-frequency of 2.5MHz in CCM and
provide the same current capacity of up to 2A. The
switching frequency is chosen to minimize the size of the
external inductor and capacitors while maintaining high
efficiency. Both channels of SC284P are independent.
where VOSTD is the pre-determined output voltage via the
CTL pins.
Operation
CFF is needed to maintain good transient response
performance. The correct value of CFF can be found using
the following equation.
During normal operation, the PMOS FET is activated on
each rising edge of the internal oscillator. The voltage
feedback loop uses an internal feedback resistor divider.
The period is set by the internal oscillator. The device has
an internal synchronous NMOS rectifier and does not
require a Schottky diode on the LXpin.
To simplify the design, it is recommended to program the
desired output voltage from a standard ꢀ.0V as shown in
Figure ꢀ with the correct CFF calculated from Equation 2.
For programming the output voltage from other standard
voltages, RFBꢀ, RFB2 and CFF need to be adjusted to meet
Equations ꢀ and 2.
Programmable Output Voltage
Both channels on SC284P have seven pre-determined
output voltage values which can be individually selected
by programming the CTL input pins (see Table ꢀ — Output
Voltage Settings). Each CTL pin has an active ꢀ MΩ internal
pull-down resistor. The ꢀMΩ resistor is switched in circuit
whenever the CTL input voltage is below the input
threshold, or when the part is in under-voltage lockout. It is
recommended to tie all high CTL pins together and use an
VINA
L
VOUTA
PVINA
LXA
RAVINA 1Ω
CINA
10µF
SC284P
CFFA
COUTA
AVINA
AGNDA
PVINB
RFB1A
CAVINA
0.1µF
external pull-up resistor to VIN if there is no enable signal, or
if the enable input is an open drain/collector signal.The CTL
pins may be driven by a microprocessor to allow dynamic
voltage adjustment for systems that reduce the supply
voltage when entering sleep states. Avoid all zeros being
present on the CTL pins when changing programmable
output voltages as this would momentarily disable the
device.
VOUTA
RFB2A
10kΩ
VINB
RFB1A = (VOUTA-1)
x RFB2A
for CTLAX = 0010
(1.0V)
RAVINB 1Ω
CINB
10µF
AVINB
L
VOUTB
CAVINB
0.1µF
LXB
AGNDB
CFFB
COUTB
PGOODA
RFB1B
PGOODA
CTL3A
Enable A
VOUTB
CTL2A
CTL1A
RFB2B
10kΩ
RFB1B = (VOUTB-1)
x RFB2B
SC284P is also capable of regulating a different (higher)
output voltage, which is not shown in the Table ꢀ, via an
external resistor divider.There will be a typical 2µA current
for CTLBX = 0010
(1.0V)
PGOODB
Enable B
PGNDA
PGNDB
PGOODB
CTL3B
CTL2B
CTL1B
flowing into the VOUT pin. The typical schematic for an ad-
justableoutputvoltageoptionfromthestandardꢀ.0Vwith
CTLX=[00ꢀ], is shown in Figure ꢀ. RFBꢀA/B and RFB2A/B are used
to adjust the desired output voltage. If the RFB2A/B current
Figure 1 — Output Voltage Programming
is such that the 2µAVOUT pin current can be ignored, then RFBꢀA/B
can be found by the next equation. RFB2A/B need to be low
ꢀ4
SC284P
Applications Information (continued)
Power Save Mode Operation
Power Good
PGOOD is an open-drain output.When the output volt-
age drops below nominal voltage, the PGOOD pin is
pulled low after a 20μs delay. During start-up, PGOOD
will be asserted ꢀ.7ms (typ.) after the output voltage
reaches 90% of the final regulation voltage.Over volt-
age, fold-back current limit and thermal shutdown will
force PGOOD low after a 20μs delay. When recovering
from a fault, PGOOD will be asserted ꢀ.7ms (typ.) af-
ter Vout reaches 90% of the final regulation voltage.
WhentheloadcurrentdecreasesbelowthePSAVEthreshold,
PWM switching stops and the device automatically enters
PSAVE mode.This threshold varies depending upon the in-
putvoltageandtheoutputvoltagesetting,optimizingeffi-
ciencyforallpossibleloadcurrentsinPWMorPSAVEmode.
While in PSAVE mode, output voltage regulation is
controlled by a series of switching bursts. During a
burst, the inductor current is limited to a peak value
which controls the on-time of the PMOS switch. Af-
ter reaching this peak, the PMOS switch is disabled
and the inductor current decreases to near 0mA.
Switching bursts continue until the output voltage climbs
to VOUT +2.5% or until the PSAVE current limit is reached.
Switching is then stopped to eliminate switching losses,
enhancing overall efficiency. Switching resumes when
the output voltage reaches the lower threshold of VOUT
and continues until the upper threshold again is reached.
Maximum Power Dissipation
Each channel of SC284P has its own ΘJA of 40°C/W when
only one channel is in operation. Since both channels are
within the same package, please make sure to use both
channelsforpowercalculations. Toguaranteeanoperating
junction temperature of less than ꢀ25°C, Figure 3 shows
the maximum allowable power loss for each channel. The
curve is based upon the junction temperature of either
channel reaching a maximum of ꢀ25°C. Each channel of
SC284P can support up to 2A load current.
Note that the output voltage is regulated hysteretically
while in PSAVE mode between VOUT and VOUT + 2.5%.
The period and duty cycle while in PSAVE mode are
solely determined by VIN and VOUT until PWM mode
resumes. This can result in the switching frequency be-
ing much lower than the PWM mode frequency. If the
output load current increases enough to cause VOUT to
decrease below the PSAVE exit threshold (VOUT-4%),
the device automatically exits PSAVE and operates in
continuous PWM mode. Note that the PSAVE high and
low threshold levels are both set at or above
VOUT to minimize undershoot when the SC284P
2.8
2.6
2.4
2.2
TA = 25°C
2
1.8
1.6
1.4
1.2
1
0.8
0.6
TA = 55°C
TA = 85°C
0.4
0.2
0
exits PSAVE mode and returns to PWM mode.
2.8
2.2 2.4 2.6
0
0.2 0.4 0.6 0.8
1
1.2 1.4 1.6 1.8
2
Load
Loss of Channel A (W)
(IOUT
)
O FF
VOU T +2.5%
Figure 3 — Maximum allowable loss for each channel
for a maximum junction temperature of 125°C
VOUT
VOU T - 4%
BURST
VLX
PSAVE
EXIT
PW M M ode at
M edium/High
Load
PSAVE M ode at
Light Load
PW M M ode at
M edium/High
Load
Tim e
Figure 2 - Transitions Between PWM and PSAVE Modes
ꢀ5
SC284P
Applications Information (continued)
Protection Features
Soft-Start
The SC284P provides the following protection features:
• Current Limit
Soft-start is activated once VIN reaches the UVLO and one
or more CTL pins are set high to enable the part. A thermal
shutdown event will also activate the soft-start sequence.
Soft-start controls the maximum current during startup
thus limiting inrush current. The PMOS current limit is
stepped through four soft-start levels of approximately
20%, 25%, 40%, & ꢀ00%. Each step is maintained for 400μs
following an internal reference start up duration of ꢀ00μs
giving a total nominal startup period of ꢀ700μs. During
startup, the chip operates by controlling the inductor
current swings between 0A and current limit. If at any time
VOUT reaches 86% of the target or at the end of the soft-
start period, the SC284P will switch to PWM mode
operation.
• Over-Voltage Protection
• Soft-Start
• Thermal Shutdown
Current Limit
The internal PMOS power device in the switching stage
is protected by a current limit feature. If the inductor
current is above the PMOS current limit for ꢀ6 consecutive
cycles, the part enters foldback current limit mode and
the output current is limited to the current limit holding
current (ICL_HOLD) of a few hundred milliampere. Under
this condition, the output voltage will be the product of
ICL_HOLD and the load resistance. The current limit holding
current will decrease when the output voltage increases.
The load presented must fall below the current limit
holding current for the part to exit foldback current
limit mode. Figure 4 shows how the typical current limit
holding current varies with output voltage. The SC284P
is capable of sustaining an indefinite short circuit without
damage and will resume normal operation when the fault
is removed. The foldback current limit mode is disabled
during soft-start.
The SC284P is capable of starting up into a pre-biased
output.
Shut Down
When all CTL pins of a channel are low, the corresponding
channel will be disabled, drawing less than ꢀμA from that
input power supply. The internal switches and bandgap
voltage will be immediately turned off.
Thermal Shutdown
300
The device has a thermal shutdown feature to protect
the SC284P if the junction temperature exceeds ꢀ60°C.
During thermal shutdown, the on-chip power devices are
disabled, tri-stating the LX output. When the temperature
drops by ꢀ0°C, it will initiate a soft-start cycle to resume
normal operation.
TA= 25°C
250
200
150
100
50
VIN= 3.6V
VIN= 5.0V
Inductor Selection
VIN= 3.3V
The SC284P converter has internal loop compensation.
The compensation is designed to work with an output
filter corner frequency of less than 40kHz for a VIN of 5V
and 50KHz for a VIN of 3.3V over any operating condition.
The corner frequency of the output filter is shown in the
following equation.
0
1.0
1.5
2.0
2.5
3.0
3.5
Output Voltage (V)
Figure 4— Typical Current Limit Holding Current
vs. Output Voltage
1
fC
2S
LuCOUT
Over-Voltage Protection
In the event of a ꢀ5% over-voltage on the output, the
PWM drive is disabled leaving the LX pin floating.
Values outside this range may lead to instability, malfunc-
tion, or out-of-specification performance.
ꢀ6
SC284P
Applications Information (continued)
L at
Dimen-
sions
LxWxH
(mm)
In general, the inductance is chosen by making the
inductor ripple current to be less than 30% of maximum
load current. When choosing an inductor, it is important
to consider the change in inductance with DC bias
current. The inductor saturation current is specified as
the current at which the inductance drops a specific
percentage from the nominal value. This is approximately
30%. Except for short-circuit or other fault conditions,
the peak current must always be less than the saturation
current specified by the manufacturer. The peak current is
the maximum load current plus one half of the inductor
ripple current at the maximum input voltage. Load and/or
line transients can cause the peak current to exceed this
level for short durations. Maintaining the peak current
below the inductor saturation specification keeps the
inductor ripple current and the output voltage ripple at
acceptable levels. Manufacturers often provide graphs of
actual inductance and saturation characteristics versus
applied inductor current. The saturation characteristics of
the inductor can vary significantly with core temperature.
Core and ambient temperatures should be considered
when examining the core saturation characteristics.
DCR
Max
(Ω)
Rated
Current
(A)
Manufacturer
Part Number
L
(μH)
Rated
Current
(μH)
TOKO
1071AS-1R0N
ꢀ.00 30% 0.040
2.20 20% 0.048
ꢀ.00 23% 0.062
2.70
2.50
2.20
0.70
ꢀ.54
0.70
2.8x3.0xꢀ.5
3.5x3.7xꢀ.8
3.2x3.2xꢀ.5
TOKO
1127AS-2R2M
Panasonic
ELLVGG1R0N
Table 2 – Recommended Inductors
COUT Selection
The internal voltage loop compensation in the SC284P
limits the minimum output capacitor value to 22µF if using
a 2.2µH inductor or 44µF if using a ꢀµH inductor.This is due
to its influence on the the loop crossover frequency, phase
margin, and gain margin. The total output capacitance
should not exceed 50µF to avoid any start-up problems.
For most typical applications it is recommended to use an
output capacitance of 22µF to 44µF. When choosing the
output capacitor’s capacitance, verify the voltage derating
effect from the capacitor vendor’s data sheet.
When the inductance has been determined, the DC
resistance (DCR) must be examined. The efficiency that
can be achieved is dependent upon the DCR of the
inductor. Lower values give higher efficiency. The RMS DC
current rating of the inductor is associated with losses in
the copper windings and the resulting temperature rise of
the inductor. This is usually specified as the current which
produces a 40˚C temperature rise. Most copper windings
are rated to accommodate this temperature rise above
maximum ambient.
Capacitors with X7R or X5R ceramic dielectric are
recommended for their low ESR and superior temperature
and voltage characteristics. Y5V capacitors should not
be used as their temperature coefficients make them
unsuitable for this application.
The output voltage droop due to a load transient is
determined by the capacitance of the ceramic output
capacitor. The ceramic capacitor supplies the load current
initially until the loop responds. Within a few switching
cycles the loop will respond and the inductor current will
increase to match the required load. The output voltage
droop during the period prior to the loop responding
can be related to the choice of output capacitor by the
relationship from the following equation.
Magnetic fields associated with the output inductor can
interfere with nearby circuitry. This can be minimized by
the use of low noise shielded inductors which use the
minimum gap possible to limit the distance that magnetic
fields can radiate from the inductor. However shielded
inductors typically have a higher DCR and are thus less
efficient than a similarly sized non-shielded inductor.
Final inductor selection depends upon various design
considerations such as efficiency, EMI, size, and cost. Table
2 lists the manufacturers of recommended inductor
options. The saturation characteristics and DC current
ratings are also shown.
ꢀu ',/2$'
9'5223 u I26&
&
287
The outputcapacitorRMSripplecurrentmaybecalculated
ꢀ7
SC284P
Applications Information (continued)
from the following equation.
§
·
9287
9
9287
9
¨
¨
¸
¸
,
ꢂꢀ
&,1ꢁ506ꢀ
,1
©
,1
¹
9
287 u
ꢀ
9
ꢂ 9287
ꢁ
§
·
The input voltage ripple and RMS current ripple are at
a maximum when the input voltage is twice the output
voltage or 50% duty cycle.
ꢄ
,1ꢁ0$;ꢀ
¨
¨
¸
¸
,
&287ꢁ506ꢀ
/ u I26& u 9
ꢃ ꢂ
©
,1
¹
Table 3 lists the manufac turers of recommended capacitor
options.
The input capacitor provides a low impedance loop for
the edges of pulsed current drawn by the PMOS switch.
Low ESR/ESL X5R ceramic capacitors are recommended
for this function. To minimize stray inductance, the capaci-
tor should be placed as close as possible to the VIN and
GND pins of the SC284P.
Value
Rated
Type Voltage
(VDC)
Dimensions
LxWxH
Manufacturer
Part Nunber
Value
(μF)
at
3.3V
(μF)
(mm)
Murataꢀ
2.0xꢀ.25xꢀ.25
(EIA:0805)
ꢀ0 ꢀ0%
ꢀ0 ꢀ0%
22 20%
47 20%
X5R
X5R
X5R
X5R
6.3
6.3
6.3
6.3
4.74
4.05
6.57
20.3
GRM21BR60J106K
Murataꢀ
2.0xꢀ.25x0.85
(EIA:0805)
GRM219R60J106K
Murataꢀ
2.0xꢀ.25xꢀ.25
(EIA:0805)
GRM21BR60J226M
Murataꢀ
3.2xꢀ.6xꢀ.6
(EIA:ꢀ206)
GRM31CR60J476M
Table 3 – Recommended Capacitors
CIN Selection
The SC284P source input current is a DC supply current
with a triangular ripple imposed on it. To prevent large
input voltage ripple, a low ESR ceramic capacitor is
required. A minimum value of ꢀ0μF should be used. It is
important to consider the DC voltage coefficient charac-
teristics when determining the actual required value. It
should be noted a ꢀ0µF, 6.3V, X5R ceramic capacitor with
5V DC applied may exhibit a capacitance as low as 4.05µF.
To estimate the required input capacitor, determine the
acceptable input ripple voltage and calculate the
minimum value required for CIN as shown by the following
equation.
§
·
9287
9
9287
9
¨
¨
¸
¸
ꢀꢀ
,1
©
,1
¹
&
,1
§
·
'9
¨
¨
¸
ꢀ (65 u I26&
¸
,
©
287
¹
The input capacitor RMS ripple current varies with the
input and output voltage. The maximum input capacitor
RMS current is found from the next equation .
ꢀ8
SC284P
Applications Information (continued)
Stages
Operation description
K
Normal PWM operation
Overload protection is enabled and peak current limit at 100% level
J
6
7
6WDJH
ꢁ
6WDJH
ꢂ
Cycle by cycle peak current limit
OCP protection is activated.
Foldback peak current limit.
6WDJH
ꢀ
8
PWM "ON" when inductor current of 0A
PWM "OFF" when inductor current hits peak current limit of foldback
mode.
M
Conditions
Operation description
Inductor current hits peak current limit
Peak current limit for 16 consecutive cycles
Vout ≥ 100% target
J
K
L
L
M
Inductor current doesn't hit peak current limit
Figure 5 — Current Limit Protection
Stages
Operation description
Chip is OFF.
0
Peak current limit at 20% level
PWM "ON" when inductor current of 0A
PWM "OFF" when inductor current hits peak current limit
Stage duration of 400µs
1
Peak current limit at 25% level
PWM "ON" when inductor current of 0A
PWM "OFF" when inductor current hits peak current limit
Stage duration of 400µs
2
3
4
%
Peak current limit at 40% level
6WDJH
ꢁ
6WDJH
ꢂ
PWM "ON" when inductor current of 500mA
PWM "OFF" when inductor current hits peak current limit
Stage duration of 400µs
$
&
6WDJH
ꢀ
Peak current limit at 100% level
PWM "ON" when inductor current of 500mA
PWM "OFF" when inductor current hits peak current limit
Stage duration of 400µs
Peak current limit at 100% level
Switch to closed-loop PWM operation.
Soft Start ends.
*
)
6WDJH
ꢃ
+
(
5
6
'
Normal PWM operation
Overload protection is enabled
6WDJH
ꢅ
6WDJH
ꢄ
Conditions
Operation description
VIN > UVLO Threshold
AND
One or more CTL pin is high.
AND
A
,
Internal reference is ready.
End of stage 1 AND Vout<86% of target
End of stage 2 AND Vout<86% of target
End of stage 3 AND Vout<86% of target
End of stage 4 AND Vout<86% of target
Vout>86% of target
Vout>86% of target
Vout>86% of target
End of soft start time of 1700µs
B
C
D
E
F
G
H
I
6WDJH
ꢆ
Figure 6 — Soft Start Operation
ꢀ9
SC284P
Applications Information (continued)
PCB Layout Considerations
The layout diagram in Figure 7 shows a recommended
PCB top layer for the SC284P and supporting components.
Figure 8 shows the bottom layer for this PCB. Fundamental
layout rules must be followed since the layout is critical for
achieving the performance specified in the Electrical
Characteristics table. Poor layout can degrade the perfor-
mance of the DC-DC converter and can contribute to EMI
problems, ground bounce, and resistive voltage losses.
Poor regulation and instability can result.
The following guidelines are recommended when devel-
oping a PCB layout:
Figure 7 — Recommended PCB Layout (Top Layer)
ꢀ. The input capacitor, CIN, should be placed as close
to the VIN and PGND pins as possible. This capacitor
provides a low impedance loop for the pulsed currents
present at the buck converter’s input. Use short wide
traces to connect as closely to the IC as possible.
This will minimize EMI and input voltage ripple by
localizing the high frequency current pulses.
2. Keep the LX pin traces as short as possible to minimize
pickup of high frequency switching edges to other
parts of the circuit. COUT and L should be connected as
close as possible between the LX and PGND pins, with
a direct return to the PGND pin from COUT
.
3. Route the output voltage feedback/sense path away
from the inductor and LX node to minimize noise and
magnetic interference.
Figure 8 — PCB Bottom Layer
4. Use a ground plane referenced to the SC284P PGND
pin. Use several vias to connect to the component
side ground to further reduce noise and interference
on sensitive circuit nodes.
5. If possible, minimize the resistance from the output
and PGND pin to the load. This will reduce the voltage
drop on the ground plane and improve the load
regulation. It will also improve the overall efficiency
by reducing the copper losses on the output and
ground planes.
C5
L2
R1 C1
C3
U1
6. Connect the AGND pins to the thermal pad.
C4
C2 R2
L1
C6
Figure 9 — Recommended PCB Layout
(Top Layer Details)
20
SC284P
Outline Drawing – 3x3 MLPQ-UT20
Land Pattern – 3x3 MLPQ-UT20
2ꢀ
SC284P
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22
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