S-8333CACC-I8T1U [SII]
STEP-UP, FOR LCD BIAS SUPPLY, 1-CHANNEL, PWM CONTROL SWITCHING REGULATOR CONTROLLER;
| 型号： | S-8333CACC-I8T1U |
| 厂家： | 
SEIKO INSTRUMENTS INC |
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S-8333 Series
STEP-UP, FOR LCD BIAS SUPPLY, 1-CHANNEL,
PWM CONTROL SWITCHING REGULATOR CONTROLLER
www.sii-ic.com
© SII Semiconductor Corporation, 2004-2015
Rev.4.2_01
The S-8333 Series is a CMOS step-up switching regulator which mainly consists of a reference voltage circuit, an oscillator,
an error amplifier, a PWM controller, an under voltage lockout circuit (UVLO), and a timer latch short-circuit protection
circuit. Because its minimum operating voltage is as low as 1.8 V, this switching regulator is ideal for the power supply of
an LCD or for portable systems that operate on a low voltage. The internal oscillation frequency can be set up to 1.08 MHz,
via the resistor connected to the ROSC pin.
The maximum duty ratio of PWM control can be controlled by the resistor connected to the RDuty pin. The soft-start
function at power application is accomplished by combining the reference voltage control and maximum duty control
methods. Even if the voltage of the FB pin is retained lower than the reference voltage due to the factor outside the IC, the
output voltage is raised by controlling the maximum duty. The phase compensation and gain value can be adjusted
according to the values of the resistor and capacitor connected to the CC pin. Therefore, the operation stability and
transient response can be correctly set for each application. The reference voltage accuracy is as high as 1.0 V 1.5%, and
any voltage can be output by using an external output voltage setting resistor.
In addition, the delay time of the short-circuit protection circuit can be set by using the capacitor connected to the CSP pin.
If the maximum duty condition continues because of short-circuiting, the capacitor externally connected to the CSP pin is
charged, and oscillation stops after a specific time. The short-circuit protection function is cancelled when the power supply
is raised to the UVLO release voltage after it has been lowered to the UVLO detection voltage. A ceramic capacitor or a
tantalum capacitor is used as the output capacitor, depending on the setting. This controller IC allows various settings and
selections and employs a small package, making it very easy to use.
Features
• Low voltage operation:
• Oscillation frequency:
• Maximum duty:
1.8 V to 6.0 V
280 kHz to 1.08 MHz (selectable by external resistor)
Settable up to 88.5% by external resistor
47 to 88.5% (oscillation frequency; 500 kHz or more)
47 to 80% (oscillation frequency; less than 500 kHz)
1.0 V 1.5%
• Reference voltage:
• Range of operation temperature: −40 to +85°C
UVLO (under-voltage lockout) function:
Detection voltage can be selected from between 1.5 V and 2.3 V in 0.1 V step.
Hysteresis width can be selected from between 0.1 V and 0.3 V in 0.1 V step.
• Timer latch short-circuit protection circuit:
Delay time can be set using an external capacitor.
•
• Soft-start function:
Soft-start time can be selected in three steps, 10 ms, 15 ms, and 20 ms.
Both reference voltage control and maximum duty control methods are applied
• Phase compensation external setting:
Control is possible via the resistor connected between the CC and GND pins
and capacitor
• Lead-free, Sn 100%, halogen-free*1
*1. Refer to “ Product Name Structure” for details.
Applications
• Power supplies for LCDs and CCDs
• Power supplies for portable equipment
Packages
• SNT-8A
• 8-Pin TSSOP
1
STEP-UP, FOR LCD BIAS SUPPLY, 1-CHANNEL, PWM CONTROL SWITCHING REGULATOR CONTROLLER
S-8333 Series
Rev.4.2_01
Block Diagram
VOUT
SD
L
RDuty
ROSC
VIN
UVLO
PWM
CFB RFB1
CL
Oscillator
Maximum duty
soft-start circuit
M1
+
−
CIN
EXT
+
comparator
Error amplifier
FB
Timer latch
−
short-circuit
Reference voltage
(1.0 V) soft-start
circuit
protection circuit
RFB2
VSS
CSP
CC
RZ CZ
Figure 1 Block Diagram
2
STEP-UP, FOR LCD BIAS SUPPLY, 1-CHANNEL, PWM CONTROL SWITCHING REGULATOR CONTROLLER
Rev.4.2_01
S-8333 Series
Product Name Structure
1. Product name
(1) SNT-8A
S-8333
C
x
x
x
-
I8T1
U
Environmental code
U:
Lead-free (Sn 100%), halogen-free
Package abbreviation and packing specifications*1
I8T1: SNT-8A, tape product
Soft-start time setting
A:
B:
C:
10 ms
15 ms
20 ms
UVLO setting
A:
B:
C:
D:
E:
F:
G:
H:
I:
2.3 V
2.2 V
2.1 V
2.0 V
1.9 V
1.8 V
1.7 V
1.6 V
1.5 V
UVLO hysteresis setting
A:
B:
C:
0.1 V
0.2 V
0.3 V
*1. Refer to the tape drawing.
3
STEP-UP, FOR LCD BIAS SUPPLY, 1-CHANNEL, PWM CONTROL SWITCHING REGULATOR CONTROLLER
S-8333 Series
Rev.4.2_01
(2) 8-Pin TSSOP
S-8333
C
x
x
x
-
T8T1
x
Environmental code
U:
S:
Lead-free (Sn 100%), halogen-free
Lead-free, halogen-free
Package abbreviation and packing specifications*1
T8T1: 8-Pin TSSOP, tape product
Soft-start time setting
A:
B:
C:
10 ms
15 ms
20 ms
UVLO setting
A:
B:
C:
D:
E:
F:
G:
H:
I:
2.3 V
2.2 V
2.1 V
2.0 V
1.9 V
1.8 V
1.7 V
1.6 V
1.5 V
UVLO hysteresis setting
A:
B:
C:
0.1 V
0.2 V
0.3 V
*1. Refer to the tape drawing.
2. Packages
Drawing Code
Tape Reel
Package Name
Package
Land
SNT-8A
PH008-A-P-SD PH008-A-C-SD PH008-A-R-SD PH008-A-L-SD
FT008-A-P-SD FT008-E-C-SD FT008-E-R-SD
8-Pin TSSOP
⎯
4
STEP-UP, FOR LCD BIAS SUPPLY, 1-CHANNEL, PWM CONTROL SWITCHING REGULATOR CONTROLLER
Rev.4.2_01
S-8333 Series
Pin Configurations
1. SNT-8A
Table 1
Top view
Pin No.
1
Symbol
CC
Description
1
2
3
4
8
7
6
5
Error amplifier circuit output phase
compensation pin
2
3
4
5
6
FB
Output voltage feedback pin
Short-circuit protection delay time setting pin
Power supply input pin
CSP
VIN
EXT
VSS
Figure 2
External transistor connection pin
GND pin
Oscillation frequency setting resistor
connection pin
7
8
ROSC
RDuty
Maximum duty setting resistor connection pin
2. 8-Pin TSSOP
Table 2
Pin No.
1
Symbol
Description
Top view
Error amplifier circuit output phase
compensation pin
CC
1
2
3
4
8
7
6
5
2
3
4
5
6
FB
Output voltage feedback pin
Short-circuit protection delay time setting pin
Power supply input pin
CSP
VIN
EXT
VSS
External transistor connection pin
GND pin
Figure 3
Oscillation frequency setting resistor
connection pin
7
8
ROSC
RDuty
Maximum duty setting resistor connection pin
5
STEP-UP, FOR LCD BIAS SUPPLY, 1-CHANNEL, PWM CONTROL SWITCHING REGULATOR CONTROLLER
S-8333 Series
Rev.4.2_01
Absolute Maximum Ratings
Table 3 Absolute Maximum Ratings
(Unless otherwise specified: Ta = 25°C, VSS = 0 V)
Parameter
VIN pin voltage
FB pin voltage
Symbol
VIN
Ratings
Unit
V
VSS − 0.3 to VSS + 6.5
VSS − 0.3 to VSS + 6.5
VSS − 0.3 to VIN + 0.3
VSS − 0.3 to VIN + 0.3
VSS − 0.3 to VIN + 0.3
10
VFB
V
EXT pin voltage
CSP pin voltage
CC pin voltage
CC pin current
VEXT
VCSP
VCC
V
V
V
ICC
mA
V
ROSC pin voltage
ROSC pin current
RDuty pin voltage
RDuty pin current
SNT-8A
VROSC
IROSC
VRDuty
IRDuty
VSS − 0.3 to VIN + 0.3
10
mA
V
VSS − 0.3 to VIN + 0.3
10
mA
mW
mW
mW
°C
°C
450*1
Power dissipation
8-Pin TSSOP
PD
300 (When not mounted on board)
700*1
Operating ambient temperature
Storage temperature
Topr
Tstg
−40 to +85
−40 to +125
*1. When mounted on board
[Mounted board]
(1) Board size: 114.3 mm × 76.2 mm × t1.6 mm
(2) Name: JEDEC STANDARD51-7
Caution
The absolute maximum ratings are rated values exceeding which the product could suffer
physical damage. These values must therefore not be exceeded under any conditions.
800
600
8-Pin TSSOP
SNT-8A
400
200
0
0
50
100
150
Ambient temperature (Ta) [°C]
Figure 4 Power Dissipation of Package (When mounted on board)
6
STEP-UP, FOR LCD BIAS SUPPLY, 1-CHANNEL, PWM CONTROL SWITCHING REGULATOR CONTROLLER
Rev.4.2_01
S-8333 Series
Electrical Characteristics
Table 4 Electrical Characteristics
(Unless otherwise specified: VIN = 3.3 V, Ta = 25°C)
Test
Circuit
Parameter
Symbol
Conditions
Min.
Typ.
Max.
Unit
Operating input voltage VIN
⎯
⎯
1.8
⎯
1.000
6.0
V
V
2
2
FB voltage
VFB
ISS1
0.985
1.015
fosc = 650 kHz
VFB = 0.95 V
Current consumption
⎯
450
700
μA
1
IEXTH
VEXT = VIN − 0.4 V
VEXT = 0.4 V
⎯
100
−100
160
−60
⎯
mA
mA
1
1
EXT pin output current
IEXTL
FB voltage temperature ΔVFB
Ta = −40 to +85°C
⎯
100
⎯
ppm/°C
μA
2
1
coefficient
ΔTa
FB pin input current
IFB
⎯
−0.1
⎯
+0.1
When fosc = 1080 kHz is set
(ROSC = 120 kΩ)
When fosc = 650 kHz is set
(ROSC = 200 kΩ)
When fosc = 280 kHz is set
(ROSC = 470 kΩ)
fosc
× 0.9
fosc
× 1.1
Oscillation frequency*1 fosc
fosc
kHz
1
VFB = 0.9 V
Waveform on EXT pin is measured.
Oscillation frequency
temperature coefficient ΔTa
Δfosc
Ta = −40 to +85°C
fosc = 650 kHz
⎯
1000
⎯
ppm/°C
1
1
fosc = 1080 kHz (ROSC = 120 kΩ)
MaxDuty = 88.5% (RDuty = 62 kΩ)
MaxDuty = 73% (RDuty = 180 kΩ)
MaxDuty = 47% (RDuty = 390 kΩ)
fosc = 650 kHz (ROSC = 200 kΩ)
MaxDuty = 88.5% (RDuty = 100 kΩ)
tSS = 10 ms, 15 ms, 20 ms
Selected in three steps
tPRO = 50 ms
MaxDuty
MaxDuty
Max. duty*2
MaxDuty
MaxDuty
%
− 5
+ 5
tSS
× 0.75
tSS
× 1.5
Soft-start time
tSS
tSS
50
ms
ms
V
1
1
1
1
Short-circuit protection
delay time*3
tPRO
37.5
75
(CSP = 0.1 μF)
VUVLO = 1.5 V to 2.3 V
Selected in 0.1 V steps
VUVLOHYS = 0.1 V to 0.3 V
Selected in 0.1 V steps
VFB = 2 V
VUVLO
× 0.95
VUVLOHYS
× 0.6
−60
34.5
VUVLO
× 1.05
VUVLOHYS
× 1.4
−34.5
60
UVLO detection voltage VUVLO
VUVLO
VUVLOHYS
UVLO hysteresis width VUVLOHYS
V
ICCH
CC pin output current
ICCL
−45
45
μA
μA
1
1
VFB = 0 V
Within short-circuit protection delay
time
VRTLT1
Timer latch reset voltage
VRTLT2
0.7
1.0
1.3
V
1
1
After short-circuit protection circuit
operated
VUVLO
× 0.95
VUVLO
× 1.05
VUVLO
V
*1. The recommended range of the resistance (Rosc) for oscillation frequency is Rosc
= 120 kΩ to 470 kΩ (fOSC = 280 kHz to 1.08 MHz).
This range of oscillation frequency is the typical value when an ideal resistor is connected externally. In actual use, it is necessary to
take account the dispersion of an IC ( 10%) into this value.
*2. Set max. duty; Between 47 and 88.5 % (RDuty/ROSC = 0.5 to 3.2); the oscillation frequency is 500 kHz or more
Between 47 and 80 % (RDuty/ROSC = 1.0 to 3.2); the oscillation frequency is less than 500 kHz
This range of max. duty is the typical value when an ideal resistor is connected externally. In actual use, it is necessary to take
account the dispersion of an IC ( 5%) into this value.
*3. The short-circuit protection time can be set by the external capacitor. Although the maximum set value by the external capacitor is
unlimited under the ideal condition, set CSP
= approx. 0.47 μF as a target maximum value due to discharge time of the capacitor.
7
STEP-UP, FOR LCD BIAS SUPPLY, 1-CHANNEL, PWM CONTROL SWITCHING REGULATOR CONTROLLER
S-8333 Series
Rev.4.2_01
External Parts When Measuring Electrical Characteristics
Table 5 External Parts
Element Name
Symbol
Manufacturer
TDK Corporation
Rohm Co., Ltd.
⎯
Part Number
LDR655312T 10 μH
RB491D
Inductor
Diode
L
SD
CL
M1
Output capacitor
Transistor
Ceramic 10 μF
Sanyo Electric Co., Ltd. MCH3406
Oscillation frequency setting resistor ROSC
⎯
⎯
200 kΩ (when fOSC = 650 kHz)
300 kΩ (when MaxDuty = 73%)
Maximum duty ratio setting resistor
Short-circuit protection delay time
setting capacitor
RDuty
CSP
⎯
0.1 μF (when tPRO = 50 ms)
Output voltage setting resistor 1
Output voltage setting resistor 2
FB pin capacitor
RFB1
RFB2
CFB
RZ
⎯
⎯
⎯
⎯
⎯
8.2 kΩ (when VOUT = 9.2 V)
1.0 kΩ (when VOUT = 9.2 V)
180 pF
Phase compensation resistor
Phase compensation capacitor
200 kΩ
0.01 μF
CZ
8
STEP-UP, FOR LCD BIAS SUPPLY, 1-CHANNEL, PWM CONTROL SWITCHING REGULATOR CONTROLLER
Rev.4.2_01
S-8333 Series
Measurement Circuits
1.
RDuty
ROSC
CC
FB
RZ
CZ
CSP
VIN
VSS
EXT
ROSC RDuty
A
CSP
CIN
Oscilloscope
Figure 5
2.
RDuty
CC
ROSC
FB
RFB1
CFB
CSP
VIN
VSS
EXT
RZ
CZ
L
SD
ROSC RDuty
RFB2
M1 CIN
CL
CSP
V
Figure 6
9
STEP-UP, FOR LCD BIAS SUPPLY, 1-CHANNEL, PWM CONTROL SWITCHING REGULATOR CONTROLLER
S-8333 Series
Rev.4.2_01
Operation
1. Switching control method
1. 1 PWM control
The S-8333 Series is a DC-DC converter using a pulse width modulation method (PWM).
The pulse width of the S-8333 Series varies from 0% to the maximum duty set by RDuty depending on the load
current, but its switching frequency does not change. Consequently, the ripple voltage generated from switching
can be removed easily via a filter.
2. Soft-start function
For this IC, the built-in soft-start circuit controls the rush current and overshoot of the output voltage when
powering on. Reference voltage adjustment and maximum duty control methods are adopted as the soft-start
methods. The following describes the soft-start function at power application.
In the circuit where the input voltage is not directly output at shutdown by inserting a switch (SW) between the
diode (SD) and VOUT output, the VOUT voltage when the VIN voltage is applied with the SW OFF stays 0 V.
Therefore, the voltage of the FB pin stays 0 V and the EXT output is in the step up status between the “H” and “L”
levels due to the maximum duty. The maximum duty at this time is approximately 7% and the rush current at
power application is controlled. The maximum duty soft start is accomplished by gradually increasing the duty
width up to the maximum duty set by the external resistor RDuty (refer to Figure 8).
The reference voltage of the error amplifier input also gradually increases from 0 V at the same time as the
maximum duty soft start. The increasing of the output voltage is controlled by turning the SW ON. The soft-start
function is realized by controlling the voltage of the FB pin so that it is the same potential as the reference voltage
that is slowly raised. A Rail-to-Rail amplifier is adopted as the error amplifier, which means that the voltage is
loop controlled so that it can be the same as the reference voltage.
Once the reference voltage rises, the voltage cannot be reset (the reference voltage is 0 V) unless making the
power supply voltage lower than the UVLO detection voltage. Conversely, when the power supply voltage rises
up to the reset voltage after it is lowered to the UVLO detection voltage or lower, the output voltage is stepped up
by the soft-start function.
SD
SW
VOUT
L
PWM
Comparator
RFB1
0.5 V
0 V
+
−
M1
VIN
CL
FB
EXT
Error amplifier
+
Error amplifier
reference voltage
CC
−
RFB2
RZ
CZ
Vref
Figure 7
10
STEP-UP, FOR LCD BIAS SUPPLY, 1-CHANNEL, PWM CONTROL SWITCHING REGULATOR CONTROLLER
Rev.4.2_01
S-8333 Series
(VIN = 0 V→3.3 V, VOUT = 9.2 V, RFB1 = 8.2 kΩ, RFB2 = 1.0 kΩ)
3.3 V
Input voltage
(VIN
)
0 V
tSS
9.2 V
Output voltage
(VOUT
VOUT×0.95
)
SW : ON
0 V
1.0 V
Error amplifier
reference voltage
0 V
Reference voltage soft-start period
1.0 V
FB pin voltage
(VFB
)
0 V
3.3 V
EXT pin voltage
(VEXT
)
0 V
Maximum duty
soft-start period
t (ms)
Figure 8
11
STEP-UP, FOR LCD BIAS SUPPLY, 1-CHANNEL, PWM CONTROL SWITCHING REGULATOR CONTROLLER
S-8333 Series
Rev.4.2_01
3. Timer latch short-circuit protection function
This IC has a timer latch short-circuit protection circuit that stops the switching operation when the output voltage
drops for a specific time due to output short-circuiting. A capacitor (CSP) that is used to set the delay time of this
short-circuit protection circuit can be connected to the CSP pin.
This IC operates at the maximum duty ratio if the output voltage drops due to output short-circuiting. At the
maximum duty ratio, constant-current charging of CSP starts. If this status lasts for a short-circuit protection
delay time and the CSP pin voltage rises above the reference voltage, the latch mode is set. Note that the latch
mode is different from the shutdown status in that the switching operation is stopped but the internal circuitry
operates normally.
To reset the latch operation to protect the IC from short-circuiting, lower VIN than the UVLO detection voltage.
The latch mode within the short-circuit protection delay time is reset by decreasing VIN to 1.0 V (Typ.) or lower.
Note that the mode is not reset even if the VIN is lowered to the UVLO detection voltage (refer to Figure 9).
UVLO release
UVLO detection
1.0 V
Input voltage
(VIN)
Output load
Short-circuit status
Reference
voltage
CSP pin voltage
(VCSP
)
50 ms (CSP = 0.1 μF)
Latch mode
Normal
status
Short-circuit
protection time
Latch
period
Short-circuit
protection time
Short-circuit
protection time
Reset period
Reset period
Figure 9
4. UVLO function
This IC includes a UVLO (under-voltage lockout) circuit to prevent the IC from malfunctioning due to a transient
status when power is applied or a momentary drop of the power supply voltage. When UVLO is in the detection
state, switching is stopped and the external FET is held in the off status. Once UVLO enters the detection state,
the soft-start function is reset.
Note that the other internal circuits operate normally and that the status is different from the power-off status.
12
STEP-UP, FOR LCD BIAS SUPPLY, 1-CHANNEL, PWM CONTROL SWITCHING REGULATOR CONTROLLER
Rev.4.2_01
S-8333 Series
5. Error amplifier
The error amplifier outputs the PWM control signal so that the voltage of the FB pin is held at a specific value
(1 V). By connecting a resistor (RZ) and capacitor (CZ) to the output pin (CC pin) of the error amplifier in series,
an optional loop gain can be set, enabling stabilized phase compensation.
6. Operation
The following are basic equations [(1) through (7)] of the step-up switching regulator (refer to Figure 10).
L
D
CONT
VOUT
VIN
EXT
M1
CL
FB
VSS
Figure 10 Step-up Switching Regulator Circuit for Basic Equations
Voltage at the CONT pin at the moment M1 is turned ON (current IL flowing through L is zero), VA:
*1
VA = VS .................................................................................................................................................(1)
*1. VS: Non-saturated voltage of M1
Change in IL over time:
dlL
dt
VL
L
VIN − VS
=
=
.............................................................................................................................(2)
L
Integration of the above equation:
V
− VS
L
IN
I =
× t ..................................................................................................................................(3)
L
IL flows while M1 is ON (ton). This time is determined by the oscillation frequency of OSC.
Peak current (IPK) after tON
:
V
− VS
L
IN
IPK
=
× t
...........................................................................................................................(4)
1
ON
The energy stored in L is represented by × L (IPK)2.
2
When M1 is turned OFF (tOFF), the energy stored in L is released via a diode, generating a reverse voltage (VL).
VL:
*2
VL
=
VOUT + VD
− VIN .........................................................................................................................(5)
*2. VD: Diode forward voltage
The voltage on the CONT pin rises only by VOUT + VD.
13
STEP-UP, FOR LCD BIAS SUPPLY, 1-CHANNEL, PWM CONTROL SWITCHING REGULATOR CONTROLLER
S-8333 Series
Rev.4.2_01
Change in current (IL) flowing through the diode into VOUT during tOFF
:
dIL
dt
VL
L
VOUT + VD − VIN
=
=
.................................................................................................................(6)
L
Integration of the above equation is as follows:
V
+ VD − VIN
L
OUT
IL = IPK
−
×t ..................................................................................................................(7)
During tON, energy is stored in L and is not transmitted to VOUT. When receiving output current (IOUT) from VOUT
,
the energy of the capacitor (CL) is used. As a result, the pin voltage of CL is reduced, and goes to the lowest level
after M1 is turned ON (tON). When M1 is turned OFF, the energy stored in L is transmitted via the diode to CL, and
the pin voltage of CL rises drastically. Because VOUT is a time function indicating the maximum value (ripple
voltage: Vp-p) when the current flowing through the diode into VOUT and the load current IOUT match.
Next, this ripple voltage is determined as follows.
IOUT vs t1 (time) from after tON, when VOUT reaches the maximum level:
V
+ VD − VIN
L
OUT
IOUT = IPK
−
× t .............................................................................................................(8)
1
L
...........................................................................................................(9)
∴t
1
=
(
IPK −IOUT
)
×
VOUT + VD − VIN
When tOFF, IL = 0 (when the energy of the inductor is completely transmitted):
Based on equation (7),
t OFF
L
=
............................................................................................................(10)
VOUT + VD − VIN
IPK
When substituting equation (10) for equation (9):
= tOFF − IOUT ×tOFF
............................................................................................................................(11)
t
1
IPK
Electrical charge ΔQ1 which is charged in CL during t1:
t1
t1
t1
VOUT + VD − VIN
VOUT + VD − VIN
1
2
2
ΔQ1 = IL dt = IPK
×
dt −
×
tdt = IPK × t1 −
×
t1 ......................(12)
0
0
0
L
L
When substituting equation (12) for equation (9):
1
IPK + IOUT
∆Q1 = IPK
−
(IPK − IOUT
)
× t1 =
× t1 ...........................................................................(13)
2
2
A rise voltage (Vp-p) due to ΔQ1:
×IPK +IOUT × t
1
∆Q1
CL
1
CL
............................................................................................................(14)
V
P - P
=
=
2
When taking into consideration IOUT consumed during t1 and ESR*1 (RESR) of CL:
∆Q1
1
IPK + IOUT
IPK + IOUT
IOUT × t1
VP−P
=
=
×
× t +
× R
−
...............................................(15)
1
ESR
CL
CL
2
2
CL
*1. Equivalent Series Resistance
When substituting equation (11) for equation (15):
2
(IPK − IOUT
)
tOFF
CL
IPK + IOUT
VP −P
=
×
+
× R
...............................................................................(16)
ESR
2 IPK
2
Therefore to reduce the ripple voltage, it is important that the capacitor connected to the output pin has a large
capacity and a small ESR.
14
STEP-UP, FOR LCD BIAS SUPPLY, 1-CHANNEL, PWM CONTROL SWITCHING REGULATOR CONTROLLER
Rev.4.2_01
S-8333 Series
External Parts Selection
1. Inductor
The inductance has a strong influence on the maximum output current (IOUT) and efficiency (η).
The peak current (IPK) increases by decreasing L and the stability of the circuit improves and IOUT increases. If L
is decreased further, the efficiency falls, and IOUT decreases if the current drive capability of the external
transistor is insufficient.
The loss of IPK by the switching transistor decreases by increasing L and the efficiency becomes maximum at a
certain L value. Further increasing L decrease the efficiency due to the loss of the DC resistance of the inductor.
IOUT also decreases.
If the oscillation frequency is higher, a smaller L value can be chosen, making the inductor smaller. In the S-8333
Series, the oscillation frequency can be varied within the range of 280 kHz to 1.08 MHz by the external resistor,
so select an L value best suited to the frequency. The recommended value is between 2.2 μH and 22 μH.
When selecting an inductor, note the allowable current of the inductor. If a current exceeding this allowable
current flows through the inductor, magnetic saturation occurs, substantially lowering the efficiency and
increasing the current, which results in damage to the IC.
Therefore, select an inductor so that IPK does not exceed the allowable current. IPK is expressed by the following
equations in the discontinuous mode and continuous mode.
2IOUT(VOUT + VD − VIN)
IPK =
( discontinuous mode ) .................................................(17)
(continuous mode) .......................................................(18)
fosc ×L
(VOUT + VD − VIN)× VIN
2×(VOUT + VD)× fosc ×L
IPK = VOUT + VD ×IOUT +
VIN
fOSC = Oscillation frequency, VD ≅ 0.4 V.
2. Diode
Use an external diode that meets the following requirements.
• Low forward voltage
• High switching speed
• Reverse breakdown voltage: VOUT + [Spike voltage] or more
• Rated current: IPK or more
3. Capacitors (CIN, CL)
The capacitor on the input side (CIN) can lower the supply impedance and level the input current for better
efficiency. Select CIN according to the impedance of the power supply to be used.
The capacitor on the output side (CL) is used to smooth the output voltage. Select an appropriate capacitance
value based on the I/O conditions and load conditions. A capacitance of 10 μF or more is recommended.
By adjusting the phase compensation of the feedback loop using the external resistor (RZ) and capacitor (CZ), a
ceramic capacitor can be used as the capacitor on the output side. If a capacitor whose equivalent series
resistance is between 30 mΩ and 500 mΩ is used as the output capacitor, the adjustable range of the phase
compensation is wider; however, note that other characteristics may be affected by ripple voltage or other
conditions at this time. The optimal capacitor differs depending on the L value, capacitance value, wiring, and
application (output load), so select the capacitor after performing sufficient evaluation under the actual usage
conditions.
15
STEP-UP, FOR LCD BIAS SUPPLY, 1-CHANNEL, PWM CONTROL SWITCHING REGULATOR CONTROLLER
S-8333 Series
Rev.4.2_01
4. External transistor
A bipolar (NPN) or enhancement (N-channel) MOS FET transistor can be used as the external capacitor.
4. 1 Bipolar (NPN) type
The driving capability when the output current is increased by using a bipolar transistor is determined by hFE
and Rb of the bipolar transistor. Figure 11 shows a peripheral circuit.
VIN
Cb
2200 pF
IPK
Pch
Nch
Rb
EXT 1 kΩ
Figure 11 External Transistor Periphery
1 kΩ is recommended for Rb. Actually, calculate the necessary base current (Ib) from hFE of the bipolar
transistor as follows and select an Rb value lower than this.
IPK
Ib =
hFE
VIN − 0.7
0.4
−
Rb =
Ib
IEXTH
A small Rb increases the output current, but the efficiency decreases. Actually, a pulsating current flows and
a voltage drop occurs due to the wiring capacitance. Determine the optimum value by experiment.
A speed-up capacitor (Cb) connected in parallel with Rb resistance as shown in Figure 11 decreases the
switching loss and improves the efficiency.
Select Cb by observing the following equation.
1
Cb ≤
2 π × Rb × fosc × 0.7
However, in practice, the optimum Cb value also varies depending on the characteristics of the bipolar
transistor employed. Therefore, determine the optimum value of Cb by experiment.
4. 2 Enhancement MOS FET type
Use an Nch power MOS FET. For high efficiency, using a MOS FET with a low ON resistance (RON) and
small input capacitance (CISS) is ideal, however, ON resistance and input capacitance generally share a
trade-off relationship. The ON resistance is efficient in a range in which the output current is relatively great
during low-frequency switching, and the input capacitance is efficient in a range in which the output current
is middling during high-frequency switching. Select a MOS FET whose ON resistance and input
capacitance are optimal depending on the usage conditions.
The input voltage (VIN) is supplied for the gate voltage of the MOS FET, so select a MOS FET with a gate
withstanding voltage that is equal to the maximum usage value of the input voltage or higher and a drain
withstanding voltage that is equal to the amount of the output voltage (VOUT) and diode voltage (VD) or
higher.
If a MOS FET with a threshold that is near the UVLO detection voltage is used, a large current may flow,
stopping the output voltage from rising and possibly generating heat in the worst case. Select a MOS FET
with a threshold that is sufficiently lower than the UVLO detection voltage value.
16
STEP-UP, FOR LCD BIAS SUPPLY, 1-CHANNEL, PWM CONTROL SWITCHING REGULATOR CONTROLLER
Rev.4.2_01
S-8333 Series
5. Oscillation frequency and maximum duty ratio setting resistors (ROSC, RDuty)
With the S-8333 Series, the oscillation frequency can be set in a range of 280 kHz to 1.08 MHz using external
resistance. Connect a resistor across the ROSC and VSS pins. Select the resistor by using the following
equation and referring to Figure 12. However, the following equation and figure assume that the resistance
value is the desired value and show the theoretical values when the IC is in the typical conditions. Note that
fluctuations of resistance and IC are not considered.
130 × 103
fOSC [kHz]
1400
ROSC [kΩ] ≅
1200
1000
800
600
400
200
0
400
600
0
200
ROSC [kΩ]
Figure 12 ROSC vs. fOSC
With the S-8333 Series, the maximum duty ratio can be set in a range of 47% to 88.5% (between 47 to 80%, if the
oscillation frequency is less than 500 kHz) by an external resistor. Connect the resistor across the RDuty and
VSS pins. Select the resistance by using the following equation and referring to Figure 13. The maximum duty
ratio fluctuates according to the oscillation frequency. If the value of ROSC is changed, therefore, be sure to
change the value of RDuty so that it is always in proportion to RDuty / ROSC. However, the following equation
and figure assume that the resistance value is the desired value and show the theoretical values when the IC is
in the typical conditions. Note that fluctuations of resistance and IC are not considered.
Caution Set max. duty 80% or less if the oscillation frequency is less than 500 kHz.
100
90
80
70
60
50
40
RDuty
ROSC
(95.5 − MaxDuty)
≅
15.0
4
0
1
2
3
RDuty / ROSC
Figure 13 RDuty / ROSC vs. MaxDuty
Connect resistors ROSC and RDuty as close to the IC as possible.
17
STEP-UP, FOR LCD BIAS SUPPLY, 1-CHANNEL, PWM CONTROL SWITCHING REGULATOR CONTROLLER
S-8333 Series
Rev.4.2_01
6. Short-circuit protection delay time setting capacitor (CSP)
With the S-8333 Series, the short-circuit protection delay time can be set to any value by an external capacitor.
Connect the capacitor across the CSP and VSS pins. Select the capacitance by using the following equation and
referring to Figure 14. However, the following equation and figure assume that the capacitor value is the desired
value and show the theoretical values when the IC is in the typical conditions. Note that fluctuations of capacitor
and IC are not considered.
3
× 2 ×
10−
120
t
PRO [ms]
1.0
CSP [μF] ≅
100
80
60
40
20
0
0.20
0
0.05
0.10
0.15
0.25
CSP [μF]
Figure 14 CSP vs. tPRO
7. Output voltage setting resistors (RFB1, RBF2)
With the S-8333 Series, the output voltage can be set to any value by external divider resistors.
Connect the divider resistors across the VOUT and VSS pins. Because VFB = 1 V, the output voltage can be
calculated by this equation.
(RFB1 + RFB2
)
VOUT
=
RFB2
Connect divider resistors RFB1 and RFB2 as close to the IC to minimize effects from of noise. If noise does have
an effect, adjust the values of RFB1 and RFB2 so that RFB1 + RFB2 < 100 kΩ.
CFB connected in parallel with RFB1 is a capacitor for phase compensation. Select the optimum value of this
capacitor at which the stable operation can be ensured from the values of the inductor and output capacitor.
8. Phase compensation setting resistor and capacitor (RZ, CZ)
The S-8333 Series needs appropriate compensation for the voltage feedback loop to prevent excessive output
ripple and unstable operation from deteriorating the efficiency. This compensation is implemented by connecting
RZ and CZ in series across the CC and VSS pins. RZ sets the high-frequency gain for a high-speed transient
response. CZ sets the pole and zero of the error amplifier and keeps the loop stable. Adjust RZ and CZ, taking
into consideration conditions such as the inductor, output capacitor, and load current, so that the optimum
transient characteristics can be obtained.
18
STEP-UP, FOR LCD BIAS SUPPLY, 1-CHANNEL, PWM CONTROL SWITCHING REGULATOR CONTROLLER
Rev.4.2_01
S-8333 Series
Standard Circuit
SD
VOUT
L
RDuty
ROSC
VIN
UVLO
PWM
CFB RFB1
CL
Oscillator
Maximum duty
soft-start circuit
M1
+
−
ROSC RDuty
CIN
EXT
+
comparator
Error amplifier
FB
Timer latch
−
0.1 μF
short-circuit
Reference voltage
(1.0 V)
soft-start circuit
protection circuit
RFB2
VSS
CSP
CC
RZ
CZ
Ground point
Figure 15 Standard Circuit
Caution
The above connection diagram and constant will not guarantee successful operation.
Perform thorough evaluation using the actual application to set the constant.
19
STEP-UP, FOR LCD BIAS SUPPLY, 1-CHANNEL, PWM CONTROL SWITCHING REGULATOR CONTROLLER
S-8333 Series
Rev.4.2_01
Precaution
•
•
Mount external capacitors, diodes, and inductor as close as possible to the IC.
Characteristics ripple voltage and spike noise occur in IC containing switching regulators. Moreover rush current
flows at the time of a power supply injection. Because these largely depend on the inductor, the capacitor and
impedance of power supply used, fully check them using an actually mounted model.
•
•
•
•
Make sure the dissipation of the switching transistor (especially at a high temperature) does not exceed the
allowable power dissipation of the package.
The performance of a switching regulator varies depending on the design of the PCB patterns, peripheral circuits,
and external parts. Thoroughly test all settings with your device.
The capacitor, diode, inductor and others used as external parts do not assure the operation at high temperature.
Evaluate fully using the actual application when designing.
This IC builds in soft start function, starts reference voltage gradually, and it is controlled so that FB pin voltage and
reference voltage become this potential. Therefore, keep in mind that it will be in a maximum duty state according
to the factor of IC exterior if FB pin voltage is held less than reference voltage.
•
•
Although the IC contains a static electricity protection circuit, static electricity or voltage that exceeds the limit of the
protection circuit should not be applied.
SII Semiconductor Corporation assumes no responsibility for the way in which this IC is used on products created
using this IC or for the specifications of that product, nor does SII Semiconductor Corporation assume any
responsibility for any infringement of patents or copyrights by products that include this IC either in Japan or in
other countries.
20
STEP-UP, FOR LCD BIAS SUPPLY, 1-CHANNEL, PWM CONTROL SWITCHING REGULATOR CONTROLLER
Rev.4.2_01
S-8333 Series
Characteristics (Typical Data)
1. Example of Major Temperature Characteristics (Ta = −40 to +85°C)
ISS1 vs. Ta (VIN = 3.3 V)
I
EXTH vs. Ta (VIN = 3.3 V)
IEXTL vs. Ta (VIN = 3.3 V)
IFB vs. Ta (VIN = 3.3 V)
fOSC vs. Ta (VIN = 3.3 V)
0.10
0.08
0.06
0.04
0.02
0
0.02
0.04
0.06
0.08
0.10
100
40 20
0
20 40 60 80
Ta [C]
MaxDuty vs. Ta (VIN = 3.3 V)
tSS vs. Ta (VIN = 3.3 V)
100
90
25.0
t
SS = 20 ms
MaxDuty = 88.5% (ROSC = 200 kRDuty = 100 k)
80
70
60
50
40
30
20
10
0
20.0
15.0
10.0
5.0
MaxDuty = 73% (ROSC = 200 kRDuty = 300 k)
MaxDuty = 47% (ROSC = 200 kRDuty = 640 k)
t
SS = 10 ms
0
100
40 20
0
20 40 60 80
Ta [C]
40 20
0
20 40 60 80 100
Ta [C]
21
STEP-UP, FOR LCD BIAS SUPPLY, 1-CHANNEL, PWM CONTROL SWITCHING REGULATOR CONTROLLER
S-8333 Series
Rev.4.2_01
tPRO vs. Ta (VIN = 3.3 V)
VUVLO vs. Ta
70.0
2.5
tPRO = 50 ms (CSP = 0.1 F)
60.0
2.0
1.5
1.0
0.5
0
50.0
40.0
30.0
20.0
10.0
0
V
UVLO = 2.3 V
UVLO = 1.5 V
V
100
40 20
0
20 40 60 80
Ta [C]
100
40 20
0
20 40 60 80
Ta [C]
VUVLOHYS vs. Ta
ICCH vs. Ta (VIN = 3.3 V)
0.35
0.30
0.25
0.20
0.15
0.10
0.05
V
UVLOHYS = 0.3 V
V
UVLOHYS = 0.1 V
0
100
40 20
0
20 40 60 80
Ta [C]
ICCL vs. Ta (VIN = 3.3 V)
VRTLT1 vs. Ta (VIN = 3.3 V)
1.2
1.0
0.8
0.6
0.4
0.2
0
100
40 20
0
20 40 60 80
Ta [C]
22
STEP-UP, FOR LCD BIAS SUPPLY, 1-CHANNEL, PWM CONTROL SWITCHING REGULATOR CONTROLLER
Rev.4.2_01
S-8333 Series
2. Example of Major Power Supply Dependence Characteristics (Ta = 25°C)
ISS1 vs. VIN
IEXTH vs. VIN
IEXTL vs. VIN
IFB vs. VIN
fOSC vs. VIN
0.10
0.08
0.06
0.04
0.02
0
0.02
0.04
0.06
0.08
0.10
7
0
1
2
3
4
5
6
VIN [V]
MaxDuty vs. VIN
tSS vs. VIN
25.0
100
90
80
70
60
50
40
30
20
10
0
20.0
15.0
10.0
5.0
MaxDuty = 88.5% (ROSC = 200 kRDuty = 100 k)
MaxDuty = 73% (ROSC = 200 kRDuty = 300 k)
tSS = 20 ms
tSS = 10 ms
MaxDuty = 47% (ROSC = 200 kRDuty = 640 k)
0
0
7
1
2
3
V
4
IN [V]
5
6
7
0
1
2
3
4
5
6
VIN [V]
23
STEP-UP, FOR LCD BIAS SUPPLY, 1-CHANNEL, PWM CONTROL SWITCHING REGULATOR CONTROLLER
S-8333 Series
Rev.4.2_01
tPRO vs. VIN
ICCH vs. VIN
70.0
tPRO=50 ms (CSP = 0.1 F)
60.0
50.0
40.0
30.0
20.0
10.0
0
7
0
1
2
3
4
5
6
VIN [V]
ICCL vs. VIN
24
STEP-UP, FOR LCD BIAS SUPPLY, 1-CHANNEL, PWM CONTROL SWITCHING REGULATOR CONTROLLER
Rev.4.2_01
S-8333 Series
3. Example of External Parts Dependence Characteristics
fOSC vs. ROSC (VIN = 3.3 V)
MaxDuty vs. RDuty / ROSC (ROSC = 200 kΩ, VIN = 3.3 V)
100
90
Ta = 40C
80
Ta = 25C
70
60
Ta = 85C
50
40
30
20
10
0
0
0.5
1
1.5
2
2.5
3
3.5
4
4.5
R
Duty / ROSC
tPRO vs. CSP (VIN = 3.3 V)
350
300
250
200
150
100
50
Ta = 40C
Ta = 25C
Ta = 85C
0
0
0.1
0.2
0.3
0.4
0.5
CSP [F]
25
STEP-UP, FOR LCD BIAS SUPPLY, 1-CHANNEL, PWM CONTROL SWITCHING REGULATOR CONTROLLER
S-8333 Series
Rev.4.2_01
4. Examples of Transient Response Characteristics
4.1 Powering ON (VOUT = 9.2 V, VIN = 0 V → 3.3 V, Ta = 25°C)
Remark The switch (SW) is inserted between the diode (SD) and VOUT output.
Controlled externally to turn SW on a few ms later after the VIN voltage is applied.
(1) fOSC = 1080 kHz, IOUT = 0 mA, tSS = 10 ms
(2) fOSC = 1080 kHz, IOUT = 100 mA, tSS = 10 ms
12
8
12
8
4
4
4
2
0
0
4
2
0
0
5
0
5
10
15
20
5
0
5
10
15
20
20
20
time [ms]
time [ms]
(3) fOSC = 650 kHz, IOUT = 0 mA, tSS = 10 ms
(4) fOSC = 650 kHz, IOUT = 100 mA, tSS = 10 ms
12
8
12
8
4
4
4
2
0
4
2
0
0
0
5
0
5
10
15
20
5
0
5
10
15
time [ms]
time [ms]
(5) fOSC = 280 kHz, IOUT = 0 mA, tSS = 10 ms
(6) fOSC = 280 kHz, IOUT = 100 mA, tSS = 10 ms
12
8
12
8
4
4
4
2
0
0
4
2
0
0
5
0
5
10
15
20
5
0
5
10
15
time [ms]
time [ms]
26
STEP-UP, FOR LCD BIAS SUPPLY, 1-CHANNEL, PWM CONTROL SWITCHING REGULATOR CONTROLLER
Rev.4.2_01
S-8333 Series
4.2 Load fluctuations (VOUT = 9.2 V, VIN = 3.3 V, Ta = 25°C, RZ = 200 kΩ, CZ = 0.01 μF)
(1) fOSC = 1080 kHz, IOUT = 0.1 mA→100 mA
(2) fOSC = 1080 kHz, IOUT = 100 mA→0.1 mA
10.0
9.8
9.6
9.4
9.2
9.0
8.8
10.0
9.8
9.6
9.4
9.2
9.0
8.8
IOUT
IOUT
100 mA
0.1 mA
100 mA
0.1 mA
V
OUT
V
OUT
[0.2 V/div]
[0.2 V/div]
20
10
0
10
20
20
20
20
10
0
10
20
20
20
time [ms]
time [ms]
(3) fOSC = 650 kHz, IOUT = 0.1 mA→100 mA
IOUT
(4) fOSC = 650 kHz, IOUT = 100 mA→0.1 mA
10.0
9.8
9.6
9.4
9.2
9.0
8.8
10.0
9.8
9.6
9.4
9.2
9.0
8.8
IOUT
100 mA
100 mA
0.1 mA
0.1 mA
VOUT
[0.2 V/div]
V
OUT
[0.2 V/div]
20
10
0
10
20
10
0
10
time [ms]
time [ms]
(5) fOSC = 280 kHz, IOUT = 0.1 mA→100 mA
(6) fOSC = 280 kHz, IOUT = 100 mA→0.1 mA
10.0
9.8
9.6
9.4
9.2
9.0
8.8
10.0
9.8
9.6
9.4
9.2
9.0
8.8
IOUT
IOUT
100 mA
0.1 mA
100 mA
0.1 mA
V
OUT
V
OUT
[0.2 V/div]
[0.2 V/div]
20
10
0
10
20
10
0
10
time [ms]
time [ms]
27
STEP-UP, FOR LCD BIAS SUPPLY, 1-CHANNEL, PWM CONTROL SWITCHING REGULATOR CONTROLLER
S-8333 Series
Rev.4.2_01
4.3 Input voltage fluctuations (VOUT = 9.2 V, IOUT = 100 mA, RZ = 200 kΩ, CZ = 0.01 μF)
(1) fOSC = 1080 kHz, VIN = 2.8 V→3.8 V
(2) fOSC = 1080 kHz, VIN = 3.8 V→2.8 V
4.0
4.0
3.5
3.0
2.5
3.5
3.0
2.5
VIN
[V]
VIN
[V]
9.40
9.30
9.20
9.10
9.40
9.30
9.20
9.10
VOUT
[V]
VOUT
[V]
20
10
0
10
20
20
10
0
10
20
time [ms]
time [ms]
(3) fOSC = 650 kHz, VIN = 2.8 V→3.8 V
(4) fOSC = 650 kHz, VIN = 3.8 V→2.8 V
4.0
4.0
3.5
3.0
2.5
3.5
3.0
2.5
V
IN
V
IN
[V]
[V]
9.40
9.30
9.20
9.10
9.40
9.30
9.20
9.10
V
OUT
V
OUT
[V]
[V]
20
10
0
10
20
20
10
0
10
20
time [ms]
time [ms]
(5) fOSC = 280 kHz, VIN = 2.8 V→3.8 V
(6) fOSC = 280 kHz, VIN = 3.8 V→2.8 V
4.0
4.0
3.5
3.0
2.5
3.5
3.0
2.5
VIN
[V]
VIN
[V]
9.40
9.30
9.20
9.10
9.40
9.30
9.20
9.10
VOUT
[V]
VOUT
[V]
20
10
0
10
20
20
10
0
10
20
time [ms]
time [ms]
28
STEP-UP, FOR LCD BIAS SUPPLY, 1-CHANNEL, PWM CONTROL SWITCHING REGULATOR CONTROLLER
Rev.4.2_01
S-8333 Series
Reference Data
1. Reference data for external parts
Table 6 Properties of External Parts
Element Name
Inductor
Product Name
LDR655312T
RB491D
Manufacture
Characteristics
*2
10 μH, DCR*1 = 307 mΩ, IMAX = 0.7 A,
TDK Corporation
Rohm Co., Ltd.
⎯
Height = 1.2 mm
*3
*4
Diode
VF = 0.45 V, IF = 1.0 A
16 V, 10 μF
Output capacitor
(ceramic)
⎯
*5
*6
*7
VDSS = 20 V, VGSS = 10 V, Ciss = 280 pF,
Transistor
MCH3406
Sanyo Electric Co., Ltd.
*8
*9
*10
RDS(ON) = 82 mΩ max. (VGS = 2.5 V, ID = 1 A)
*1. DCR :
DC resistance
*2. IMAX
*3. VF :
*4. IF :
:
Maximum allowable current
Forward voltage
Forward current
*5. VDSS
:
:
Drain to source voltage (when short circuited between the gate and source)
Gate to source voltage (when short circuited between the drain and source)
Input capacitance
*6. VGSS
*7. Ciss
:
*8. RDS(ON) : Drain to source on resistance
*9. VGS
*10. ID :
:
Gate to source voltage
Drain current
Caution The values shown in the characteristics column of Table 6 above are based on the materials
provided by each manufacturer. However, consider the characteristics of the original materials
when using the above products.
29
STEP-UP, FOR LCD BIAS SUPPLY, 1-CHANNEL, PWM CONTROL SWITCHING REGULATOR CONTROLLER
S-8333 Series
Rev.4.2_01
2. Reference data (1)
The data of (a) output current (IOUT) vs. efficiency (η) characteristics and (b) output current (IOUT) vs. output voltage
(VOUT) characteristics is shown below.
2. 1 VOUT = 13.1 V (RFB1 = 7.5 kΩ, RFB2 = 620 Ω)
(1) fOSC = 1080 kHz, MaxDuty = 73% (ROSC = 120 kΩ, RDuty = 180 kΩ)
(a) IOUT vs. η
(b) IOUT vs. VOUT
13.20
100
90
80
70
60
50
40
30
20
10
0
13.15
13.10
13.05
13.00
12.95
V
IN = 5.0 V
VIN = 5.0 V
12.90
0.01
0.1
0.1
0.1
1
10
100
1000
0.01
0.1
1
10
100
1000
IOUT [mA]
IOUT [mA]
(2) fOSC = 650 kHz, MaxDuty = 73% (ROSC = 200 kΩ, RDuty = 300 kΩ)
(a) IOUT vs. η
(b) IOUT vs. VOUT
13.20
13.15
13.10
13.05
13.00
12.95
12.90
100
90
80
70
60
50
40
30
20
10
0
V
IN = 5.0 V
VIN = 5.0 V
0.01
1
10
100
1000
0.01
0.1
1
10
100
1000
IOUT [mA]
IOUT [mA]
(3) fOSC = 280 kHz, MaxDuty = 73% (ROSC = 470 kΩ, RDuty = 750 kΩ)
(a) IOUT vs. η
(b) IOUT vs. VOUT
100
90
80
70
60
50
40
30
20
10
0
13.20
13.15
13.10
13.05
13.00
12.95
V
IN = 5.0 V
VIN = 5.0 V
12.90
0.01
0.01
0.1
1
10
100
1000
1
10
100
1000
IOUT [mA]
IOUT [mA]
30
STEP-UP, FOR LCD BIAS SUPPLY, 1-CHANNEL, PWM CONTROL SWITCHING REGULATOR CONTROLLER
Rev.4.2_01
S-8333 Series
2. 2 VOUT = 9.2 V (RFB1 = 8.2 kΩ, RFB2 = 1.0 kΩ)
(1) fOSC = 1080 kHz, MaxDuty = 73% (ROSC = 120 kΩ, RDuty = 180 kΩ)
(a) IOUT vs. η
(b) IOUT vs. VOUT
9.30
9.25
9.20
9.15
9.10
9.05
9.00
100
90
80
70
60
50
40
30
20
10
0
V
V
IN = 3.3 V
IN = 5.0 V
V
V
IN = 3.3 V
IN = 5.0 V
0.01
0.1
1
10
100
1000
0.01
0.1
1
10
100
1000
IOUT [mA]
IOUT [mA]
(2) fOSC = 650 kHz, MaxDuty = 73% (ROSC = 200 kΩ, RDuty = 300 kΩ)
(a) IOUT vs. η
(b) IOUT vs. VOUT
9.30
100
90
80
70
60
50
40
30
20
10
0
9.25
9.20
9.15
9.10
9.05
V
V
IN = 3.3 V
IN = 5.0 V
V
V
IN = 3.3 V
IN = 5.0 V
9.00
0.01
0.1
1
10
100
1000
0.01
0.1
1
10
100
1000
IOUT [mA]
IOUT [mA]
(3) fOSC = 280 kHz, MaxDuty = 73% (ROSC = 470 kΩ, RDuty = 750 kΩ)
(a) IOUT vs. η
(b) IOUT vs. VOUT
100
90
80
70
60
50
40
30
20
10
0
9.30
9.25
9.20
9.15
9.10
9.05
9.00
V
V
IN = 3.3 V
IN = 5.0 V
V
V
IN = 3.3 V
IN = 5.0 V
0.01
0.1
1
10
100
1000
0.01
0.1
1
10
100
1000
IOUT [mA]
IOUT [mA]
31
STEP-UP, FOR LCD BIAS SUPPLY, 1-CHANNEL, PWM CONTROL SWITCHING REGULATOR CONTROLLER
S-8333 Series
Rev.4.2_01
2. 3 VOUT = 6.1 V (RFB1 = 5.1 kΩ, RFB2 = 1.0 kΩ)
(1) fOSC = 1080 kHz, MaxDuty = 73% (ROSC = 120 kΩ, RDuty = 180 kΩ)
(a) IOUT vs. η
(b) IOUT vs. VOUT
100
90
80
70
60
50
40
30
20
10
0
6.20
6.15
6.10
6.05
6.00
5.95
5.90
V
V
IN = 2.5 V
IN = 3.3 V
V
V
IN = 2.5 V
IN = 3.3 V
0.01
0.1
1
10
100
1000
0.01
0.1
0.1
0.1
1
10
10
10
100
1000
IOUT [mA]
I
OUT [mA]
(2) fOSC = 650 kHz, MaxDuty = 73% (ROSC = 200 kΩ, RDuty = 300 kΩ)
(a) IOUT vs. η
(b) IOUT vs. VOUT
100
90
80
70
60
50
40
30
20
10
0
6.20
6.15
6.10
6.05
6.00
5.95
V
V
IN = 2.5 V
IN = 3.3 V
V
V
IN = 2.5 V
IN = 3.3 V
5.90
0.01
0.01
0.1
1
10
100
1000
1
100
1000
IOUT [mA]
I
OUT [mA]
(3) fOSC = 280 kHz, MaxDuty = 73% (ROSC = 470 kΩ, RDuty = 750 kΩ)
(a) IOUT vs. η
(b) IOUT vs. VOUT
100
90
80
70
60
50
40
30
20
10
0
6.20
6.15
6.10
6.05
6.00
5.95
5.90
V
V
IN = 2.5 V
IN = 3.3 V
V
V
IN = 2.5 V
IN = 3.3 V
0.01
0.1
1
10
100
1000
0.01
1
100
1000
IOUT [mA]
I
OUT [mA]
32
STEP-UP, FOR LCD BIAS SUPPLY, 1-CHANNEL, PWM CONTROL SWITCHING REGULATOR CONTROLLER
Rev.4.2_01
S-8333 Series
3. Reference data (2)
The data of output current (IOUT) vs. ripple voltage (Vr) characteristics is shown below.
3. 1 VOUT = 13.1 V (RFB1 = 7.5 kΩ, RFB2 = 620 Ω)
(1) fOSC = 1080 kHz, MaxDuty = 73 %
(ROSC = 120 kΩ, RDuty = 180 kΩ)
100
(2) fOSC = 650 kHz, MaxDuty = 73%
(ROSC = 200 kΩ, RDuty = 300 kΩ)
100
90
80
70
60
50
40
30
20
10
0
90
VIN = 5.0 V
V
IN = 5.0 V
80
70
60
50
40
30
20
10
0
0.01
0.1
1
10
100
1000
0.01
0.1
1
10
100
1000
IOUT [mA]
IOUT [mA]
(3) fOSC = 280 kHz, MaxDuty = 73%
(ROSC = 470 kΩ, RDuty = 750 kΩ)
100
90
80
70
60
50
40
30
20
10
0
V
IN = 5.0 V
0.01
0.1
1
10
100
1000
IOUT [mA]
3. 2 VOUT = 9.2 V (RFB1 = 8.2 kΩ, RFB2 = 1.0 kΩ)
(1) fOSC = 1080 kHz, MaxDuty = 73%
(ROSC = 120 kΩ, RDuty = 180 kΩ)
100
(2) fOSC = 650 kHz, MaxDuty = 73%
(ROSC = 200 kΩ, RDuty = 300 kΩ)
100
90
80
70
60
50
40
30
20
10
0
90
80
70
60
50
40
30
20
10
0
V
IN = 3.3 V
IN = 5.0 V
V
V
IN = 3.3 V
IN = 5.0 V
V
0.01
0.1
1
10
100
1000
0.01
0.1
1
10
100
1000
IOUT [mA]
IOUT [mA]
(3) fOSC = 280 kHz, MaxDuty = 73%
(ROSC = 470 kΩ, RDuty = 750 kΩ)
100
V
V
IN = 3.3 V
IN = 5.0 V
90
80
70
60
50
40
30
20
10
0
0.01
0.1
1
10
100
1000
IOUT [mA]
33
STEP-UP, FOR LCD BIAS SUPPLY, 1-CHANNEL, PWM CONTROL SWITCHING REGULATOR CONTROLLER
S-8333 Series
Rev.4.2_01
3. 3 VOUT = 6.1 V (RFB1 = 5.1 kΩ, RFB2 = 1.0 kΩ)
(1) fOSC = 1080 kHz, MaxDuty = 73%
(ROSC = 120 kΩ, RDuty = 180 kΩ)
100
(2) fOSC = 650 kHz, MaxDuty = 73%
(ROSC = 200 kΩ, RDuty = 300 kΩ)
100
VIN = 2.5 V
IN = 3.3 V
90
80
70
60
50
40
30
20
10
0
V
V
IN = 2.5 V
IN = 3.3 V
90
80
70
60
50
40
30
20
10
0
V
0.01
0.1
1
10
100
1000
0.01
0.1
1
10
100
1000
IOUT [mA]
IOUT [mA]
(3) fOSC = 280 kHz, MaxDuty = 73%
(ROSC = 470 kΩ, RDuty = 750 kΩ)
100
VIN = 2.5 V
VIN = 3.3 V
90
80
70
60
50
40
30
20
10
0
0.01
0.1
1
10
100
1000
I
OUT [mA]
34
STEP-UP, FOR LCD BIAS SUPPLY, 1-CHANNEL, PWM CONTROL SWITCHING REGULATOR CONTROLLER
Rev.4.2_01
S-8333 Series
Marking Specifications
1. SNT-8A
Top view
(1):
Blank
8
7
6
5
(2) to (4):
(5), (6):
(7) to (11):
Product code (Refer to Product name vs. Product code)
Blank
Lot number
(1) (2) (3) (4)
(5) (6) (7) (8)
(9) (10) (11
)
1
2
3
4
Product name vs. Product code
Product code
Product code
Product name
Product name
(2)
(3)
2
2
2
2
2
2
2
2
2
2
2
2
2
2
2
2
2
2
2
2
2
2
2
2
2
2
2
3
3
3
3
3
3
3
3
3
3
3
3
3
3
(4)
A
B
C
D
E
F
G
H
I
(2)
U
U
U
U
U
U
U
U
U
U
U
U
U
U
U
U
U
U
U
U
U
U
U
U
U
U
U
U
U
U
U
U
U
U
U
U
U
U
U
U
(3)
3
3
3
3
3
3
3
3
3
3
3
3
3
4
4
4
4
4
4
4
4
4
4
4
4
4
4
4
4
4
4
4
4
4
4
4
4
4
4
4
(4)
O
P
Q
R
S
T
U
V
W
X
Y
Z
S-8333CAAA-I8T1U
S-8333CAAB-I8T1U
S-8333CAAC-I8T1U
S-8333CABA-I8T1U
S-8333CABB-I8T1U
S-8333CABC-I8T1U
S-8333CACA-I8T1U
S-8333CACB-I8T1U
S-8333CACC-I8T1U
S-8333CADA-I8T1U
S-8333CADB-I8T1U
S-8333CADC-I8T1U
S-8333CAEA-I8T1U
S-8333CAEB-I8T1U
S-8333CAEC-I8T1U
S-8333CAFA-I8T1U
S-8333CAFB-I8T1U
S-8333CAFC-I8T1U
S-8333CAGA-I8T1U
S-8333CAGB-I8T1U
S-8333CAGC-I8T1U
S-8333CAHA-I8T1U
S-8333CAHB-I8T1U
S-8333CAHC-I8T1U
S-8333CAIA-I8T1U
S-8333CAIB-I8T1U
S-8333CAIC-I8T1U
S-8333CBAA-I8T1U
S-8333CBAB-I8T1U
S-8333CBAC-I8T1U
S-8333CBBA-I8T1U
S-8333CBBB-I8T1U
S-8333CBBC-I8T1U
S-8333CBCA-I8T1U
S-8333CBCB-I8T1U
S-8333CBCC-I8T1U
S-8333CBDA-I8T1U
S-8333CBDB-I8T1U
S-8333CBDC-I8T1U
S-8333CBEA-I8T1U
S-8333CBEB-I8T1U
U
U
U
U
U
U
U
U
U
U
U
U
U
U
U
U
U
U
U
U
U
U
U
U
U
U
U
U
U
U
U
U
U
U
U
U
U
U
U
U
U
S-8333CBEC-I8T1U
S-8333CBFA-I8T1U
S-8333CBFB-I8T1U
S-8333CBFC-I8T1U
S-8333CBGA-I8T1U
S-8333CBGB-I8T1U
S-8333CBGC-I8T1U
S-8333CBHA-I8T1U
S-8333CBHB-I8T1U
S-8333CBHC-I8T1U
S-8333CBIA-I8T1U
S-8333CBIB-I8T1U
S-8333CBIC-I8T1U
S-8333CCAA-I8T1U
S-8333CCAB-I8T1U
S-8333CCAC-I8T1U
S-8333CCBA-I8T1U
S-8333CCBB-I8T1U
S-8333CCBC-I8T1U
S-8333CCCA-I8T1U
S-8333CCCB-I8T1U
S-8333CCCC-I8T1U
S-8333CCDA-I8T1U
S-8333CCDB-I8T1U
S-8333CCDC-I8T1U
S-8333CCEA-I8T1U
S-8333CCEB-I8T1U
S-8333CCEC-I8T1U
S-8333CCFA-I8T1U
S-8333CCFB-I8T1U
S-8333CCFC-I8T1U
S-8333CCGA-I8T1U
S-8333CCGB-I8T1U
S-8333CCGC-I8T1U
S-8333CCHA-I8T1U
S-8333CCHB-I8T1U
S-8333CCHC-I8T1U
S-8333CCIA-I8T1U
S-8333CCIB-I8T1U
S-8333CCIC-I8T1U
J
K
L
M
N
O
P
Q
R
S
T
U
V
W
X
Y
Z
3
A
B
C
D
E
F
G
H
I
J
K
L
M
N
O
P
Q
R
S
T
U
V
W
X
Y
Z
3
A
B
C
D
E
F
G
H
I
J
K
L
M
N
3
35
STEP-UP, FOR LCD BIAS SUPPLY, 1-CHANNEL, PWM CONTROL SWITCHING REGULATOR CONTROLLER
S-8333 Series
Rev.4.2_01
2. 8-Pin TSSOP
Top view
(1) to (4):
(5) to (8):
(9) to (14): Lot number
Product name: 8333 (Fixed)
Function code (Refer to Product name vs. Function code)
1
2
3
4
8
7
6
5
(1) (2) (3) (4)
(5) (6) (7) (8)
(9) (10) (11) (12) (13) (14
)
Product name vs. Function code
Function code
(5) (6) (7) (8)
Function code
Product name
Product name
(5)
C
C
C
C
C
C
C
C
C
C
C
C
C
C
C
C
C
C
C
C
C
C
C
C
C
C
C
C
C
C
C
C
C
C
C
C
C
C
C
C
(6)
B
B
B
B
B
B
B
B
B
B
B
B
B
C
C
C
C
C
C
C
C
C
C
C
C
C
C
C
C
C
C
C
C
C
C
C
C
C
C
C
(7)
E
F
F
F
G
G
G
H
H
H
I
(8)
C
A
B
C
A
B
C
A
B
C
A
B
C
A
B
C
A
B
C
A
B
C
A
B
C
A
B
C
A
B
C
A
B
C
A
B
C
A
B
C
S-8333CAAA-T8T1y
S-8333CAAB-T8T1y
S-8333CAAC-T8T1y
S-8333CABA-T8T1y
S-8333CABB-T8T1y
S-8333CABC-T8T1y
S-8333CACA-T8T1y
S-8333CACB-T8T1y
S-8333CACC-T8T1y
S-8333CADA-T8T1y
S-8333CADB-T8T1y
S-8333CADC-T8T1y
S-8333CAEA-T8T1y
S-8333CAEB-T8T1y
S-8333CAEC-T8T1y
S-8333CAFA-T8T1y
S-8333CAFB-T8T1y
S-8333CAFC-T8T1y
S-8333CAGA-T8T1y
S-8333CAGB-T8T1y
S-8333CAGC-T8T1y
S-8333CAHA-T8T1y
S-8333CAHB-T8T1y
S-8333CAHC-T8T1y
S-8333CAIA-T8T1y
S-8333CAIB-T8T1y
S-8333CAIC-T8T1y
S-8333CBAA-T8T1y
S-8333CBAB-T8T1y
S-8333CBAC-T8T1y
S-8333CBBA-T8T1y
S-8333CBBB-T8T1y
S-8333CBBC-T8T1y
S-8333CBCA-T8T1y
S-8333CBCB-T8T1y
S-8333CBCC-T8T1y
S-8333CBDA-T8T1y
S-8333CBDB-T8T1y
S-8333CBDC-T8T1y
S-8333CBEA-T8T1y
S-8333CBEB-T8T1y
C
C
C
C
C
C
C
C
C
C
C
C
C
C
C
C
C
C
C
C
C
C
C
C
C
C
C
C
C
C
C
C
C
C
C
C
C
C
C
C
C
A
A
A
A
A
A
A
A
A
A
A
A
A
A
A
A
A
A
A
A
A
A
A
A
A
A
A
B
B
B
B
B
B
B
B
B
B
B
B
B
B
A
A
A
B
B
B
C
C
C
D
D
D
E
E
E
F
F
F
G
G
G
H
H
H
I
A
B
C
A
B
C
A
B
C
A
B
C
A
B
C
A
B
C
A
B
C
A
B
C
A
B
C
A
B
C
A
B
C
A
B
C
A
B
C
A
B
S-8333CBEC-T8T1y
S-8333CBFA-T8T1y
S-8333CBFB-T8T1y
S-8333CBFC-T8T1y
S-8333CBGA-T8T1y
S-8333CBGB-T8T1y
S-8333CBGC-T8T1y
S-8333CBHA-T8T1y
S-8333CBHB-T8T1y
S-8333CBHC-T8T1y
S-8333CBIA-T8T1y
S-8333CBIB-T8T1y
S-8333CBIC-T8T1y
S-8333CCAA-T8T1y
S-8333CCAB-T8T1y
S-8333CCAC-T8T1y
S-8333CCBA-T8T1y
S-8333CCBB-T8T1y
S-8333CCBC-T8T1y
S-8333CCCA-T8T1y
S-8333CCCB-T8T1y
S-8333CCCC-T8T1y
S-8333CCDA-T8T1y
S-8333CCDB-T8T1y
S-8333CCDC-T8T1y
S-8333CCEA-T8T1y
S-8333CCEB-T8T1y
S-8333CCEC-T8T1y
S-8333CCFA-T8T1y
S-8333CCFB-T8T1y
S-8333CCFC-T8T1y
S-8333CCGA-T8T1y
S-8333CCGB-T8T1y
S-8333CCGC-T8T1y
S-8333CCHA-T8T1y
S-8333CCHB-T8T1y
S-8333CCHC-T8T1y
S-8333CCIA-T8T1y
S-8333CCIB-T8T1y
S-8333CCIC-T8T1y
I
I
A
A
A
B
B
B
C
C
C
D
D
D
E
E
E
F
F
F
G
G
G
H
H
H
I
I
I
A
A
A
B
B
B
C
C
C
D
D
D
E
E
I
I
Remark 1. y: S or U
2. Please select products of environmental code = U for Sn 100%, halogen-free products.
36
1.97±0.03
6
5
8
7
+0.05
-0.02
0.08
1
2
3
4
0.5
0.48±0.02
0.2±0.05
No. PH008-A-P-SD-2.0
SNT-8A-A-PKG Dimensions
PH008-A-P-SD-2.0
TITLE
No.
SCALE
UNIT
mm
SII Semiconductor Corporation
+0.1
-0
4.0±0.1
2.0±0.05
0.25±0.05
ø1.5
0.65±0.05
ø0.5±0.1
4.0±0.1
2.25±0.05
5°
4 3 2 1
5 6 7 8
Feed direction
No. PH008-A-C-SD-1.0
SNT-8A-A-Carrier Tape
PH008-A-C-SD-1.0
TITLE
No.
SCALE
UNIT
mm
SII Semiconductor Corporation
12.5max.
9.0±0.3
Enlarged drawing in the central part
ø13±0.2
(60°)
(60°)
No. PH008-A-R-SD-1.0
SNT-8A-A-Reel
TITLE
PH008-A-R-SD-1.0
No.
SCALE
UNIT
5,000
QTY.
mm
SII Semiconductor Corporation
0.52
2
2.01
0.52
1
0.2
0.3
1.
2.
(0.25 mm min. / 0.30 mm typ.)
(1.96 mm ~ 2.06 mm)
1.
2.
0.03 mm
3.
4.
SNT
1. Pay attention to the land pattern width (0.25 mm min. / 0.30 mm typ.).
2. Do not widen the land pattern to the center of the package (1.96 mm to 2.06mm).
Caution 1. Do not do silkscreen printing and solder printing under the mold resin of the package.
2. The thickness of the solder resist on the wire pattern under the package should be 0.03 mm
or less from the land pattern surface.
3. Match the mask aperture size and aperture position with the land pattern.
4. Refer to "SNT Package User's Guide" for details.
(0.25 mm min. / 0.30 mm typ.)
(1.96 mm ~ 2.06 mm)
1.
2.
SNT-8A-A
-Land Recommendation
TITLE
No. PH008-A-L-SD-4.1
PH008-A-L-SD-4.1
No.
SCALE
UNIT
mm
SII Semiconductor Corporation
+0.3
-0.2
3.00
5
8
1
4
0.17±0.05
0.2±0.1
0.65
No. FT008-A-P-SD-1.1
TSSOP8-E-PKG Dimensions
FT008-A-P-SD-1.1
TITLE
No.
SCALE
UNIT
mm
SII Semiconductor Corporation
4.0±0.1
2.0±0.05
ø1.55±0.05
0.3±0.05
+0.1
-0.05
8.0±0.1
ø1.55
(4.4)
+0.4
-0.2
6.6
8
1
4
5
Feed direction
No. FT008-E-C-SD-1.0
TITLE
TSSOP8-E-Carrier Tape
FT008-E-C-SD-1.0
No.
SCALE
UNIT
mm
SII Semiconductor Corporation
13.4±1.0
17.5±1.0
Enlarged drawing in the central part
ø21±0.8
2±0.5
ø13±0.5
No. FT008-E-R-SD-1.0
TSSOP8-E-Reel
FT008-E-R-SD-1.0
TITLE
No.
SCALE
UNIT
QTY.
3,000
mm
SII Semiconductor Corporation
Disclaimers (Handling Precautions)
1. All the information described herein (product data, specifications, figures, tables, programs, algorithms and
application circuit examples, etc.) is current as of publishing date of this document and is subject to change without
notice.
2. The circuit examples and the usages described herein are for reference only, and do not guarantee the success of
any specific mass-production design.
SII Semiconductor Corporation is not responsible for damages caused by the reasons other than the products or
infringement of third-party intellectual property rights and any other rights due to the use of the information described
herein.
3. SII Semiconductor Corporation is not responsible for damages caused by the incorrect information described herein.
4. Take care to use the products described herein within their specified ranges. Pay special attention to the absolute
maximum ratings, operation voltage range and electrical characteristics, etc.
SII Semiconductor Corporation is not responsible for damages caused by failures and/or accidents, etc. that occur
due to the use of products outside their specified ranges.
5. When using the products described herein, confirm their applications, and the laws and regulations of the region or
country where they are used and verify suitability, safety and other factors for the intended use.
6. When exporting the products described herein, comply with the Foreign Exchange and Foreign Trade Act and all
other export-related laws, and follow the required procedures.
7. The products described herein must not be used or provided (exported) for the purposes of the development of
weapons of mass destruction or military use. SII Semiconductor Corporation is not responsible for any provision
(export) to those whose purpose is to develop, manufacture, use or store nuclear, biological or chemical weapons,
missiles, or other military use.
8. The products described herein are not designed to be used as part of any device or equipment that may affect the
human body, human life, or assets (such as medical equipment, disaster prevention systems, security systems,
combustion control systems, infrastructure control systems, vehicle equipment, traffic systems, in-vehicle equipment,
aviation equipment, aerospace equipment, and nuclear-related equipment), excluding when specified for in-vehicle
use or other uses. Do not use those products without the prior written permission of SII Semiconductor Corporation.
Especially, the products described herein cannot be used for life support devices, devices implanted in the human
body and devices that directly affect human life, etc.
Prior consultation with our sales office is required when considering the above uses.
SII Semiconductor Corporation is not responsible for damages caused by unauthorized or unspecified use of our
products.
9. Semiconductor products may fail or malfunction with some probability.
The user of these products should therefore take responsibility to give thorough consideration to safety design
including redundancy, fire spread prevention measures, and malfunction prevention to prevent accidents causing
injury or death, fires and social damage, etc. that may ensue from the products' failure or malfunction.
The entire system must be sufficiently evaluated and applied on customer's own responsibility.
10. The products described herein are not designed to be radiation-proof. The necessary radiation measures should be
taken in the product design by the customer depending on the intended use.
11. The products described herein do not affect human health under normal use. However, they contain chemical
substances and heavy metals and should therefore not be put in the mouth. The fracture surfaces of wafers and chips
may be sharp. Take care when handling these with the bare hands to prevent injuries, etc.
12. When disposing of the products described herein, comply with the laws and ordinances of the country or region where
they are used.
13. The information described herein contains copyright information and know-how of SII Semiconductor Corporation.
The information described herein does not convey any license under any intellectual property rights or any other
rights belonging to SII Semiconductor Corporation or a third party. Reproduction or copying of the information
described herein for the purpose of disclosing it to a third-party without the express permission of SII Semiconductor
Corporation is strictly prohibited.
14. For more details on the information described herein, contact our sales office.
1.0-2016.01
www.sii-ic.com
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