TS635DW [STMICROELECTRONICS]
DUAL WIDE BAND OPERATIONAL AMPLIFIER FOR ADSL LINE INTERFACE; 双宽频带运算放大器，用于ADSL线路接口
| 型号： | TS635DW |
| 厂家： | 
ST |
| 描述： | DUAL WIDE BAND OPERATIONAL AMPLIFIER FOR ADSL LINE INTERFACE |
| 文件： | 总10页 (文件大小：129K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
TS635
DUAL WIDE BAND OPERATIONAL AMPLIFIER
FOR ADSL LINE INTERFACE
■ LOW NOISE : 3.2nV/√Hz, 1.5pA/√Hz
■ HIGH OUTPUT CURRENT : 160mA min.
■ VERY LOW HARMONIC AND INTERMODU-
LATION DISTORTION
D
SO8
■ HIGH SLEW RATE : 40V/µs
■ SPECIFIED FOR 25Ω LOAD
(Plastic Micropackage)
DESCRIPTION
This device is particularly intended for applications
where multiple carriers must be amplified simulta-
neously with very low intermodulation products. It
has been mainly designed to fit with ADSL
chip-set such as ST70134 or ST70135.
DW
SO8 Exposed-Pad
(Plastic Micropackage)
The TS635 is a high output current dual operation-
al amplifier, with a large gain-bandwidth product
(130MHz) and capable of driving a 25Ω load at
12V power supply. The TS635 is fitted out with
Power Down function in order to decrease the
consumption.
PIN CONNECTIONS (top view)
The TS635 is housed in a SO8 plastic package
and a SO8 Exposed-Pad plastic package.
Output1
VCC +
1
2
3
4
8
7
6
5
APPLICATION
_
+
Inverting Input1
Non Inverting Input1
VCC -
Output2
■ UPSTREAM line driver for Asymmetric Digital
_
+
Inverting Input2
Non Inverting Input2
Subscriber Line (ADSL) (NT).
ORDER CODE
Package
Part
Temperature
Range
Cross Section View Showing Exposed-Pad
This pad can be connected to a (-Vcc) copper area on the PCB
Number
D
DW
TS635ID
-40, +85°C
-40, +85°C
•
TS635IDW
•
D = Small Outline Package (SO) - also available in Tape & Reel (DT)
DW = Small Outline Package in Exposed-Pad (SO) - also available in
Tape & Reel (DWT)
December 2002
1/10
TS635
ABSOLUTE MAXIMUM RATINGS
Symbol
Parameter
Value
Unit
1)
V
±7
±2
V
V
Supply voltage
CC
2)
V
Differential Input Voltage
id
in
3)
V
±6
V
Input Voltage Range
T
Operating Free Air Temperature Range TS635ID
Storage Temperature
-40 to + 85
-65 to +150
150
°C
°C
°C
oper
T
std
T
Maximum Junction Temperature
j
SO8
R
Thermal Resistance Junction to Case
Thermal Resistance Junction to Ambient Area
Maximum Power Dissipation (@25°C)
28
°C/W
°C/W
mW
thjc
thja
R
175
715
Pmax.
SO8 Exposed-Pad
R
R
Thermal Resistance Junction to Case
Thermal Resistance Junction to Ambient Area
Maximum Power Dissipation (@25°C)
16
60
°C/W
°C/W
mW
thjc
thja
Pmax.
2000
1. All voltages values, except differential voltage are with respect to network terminal.
2. Differential voltages are non-inverting input terminal with respect to the inverting input terminal.
3. The magnitude of input and output voltages must never exceed V
+0.3V.
CC
OPERATING CONDITIONS
Symbol
Parameter
Value
±2.5 to ±6
Unit
V
V
Supply Voltage
Common Mode Input Voltage
CC
+
V
V
(V ) +2 to (V
) -1
icm
CC
CC
APPLICATION: ADSL LINE INTERFACE
TS635
Line Driver
ASCOT ADSL
CHIP-SET
TX
LP filter
upstream
emission
(analog
signal)
HYBRID
CIRCUIT
ST70135
ST70134
Power Down
twisted-pair
telephone
line
RX
downstream
TS636
VGA
reception
(analog signal)
Receiver
4-bit Gain Control
2/10
TS635
ELECTRICAL CHARACTERISTICS. VCC = ±6V, Tamb = 25°C (unless otherwise specified).
Symbol
Parameter
Test Condition
Min.
Typ.
Max
Unit
DC PERFORMANCE
∆Vio
T
amb = 25°C
Tamb
Tmin. < Tamb < Tmax.
Tamb
Differential Input Offset Voltage
6
3
mV
0.2
5
Iio
Input Offset Current
µA
5
15
30
Iib
Input Bias Current
µA
Tmin. < Tamb < Tmax.
Vic = 2V to 2V, Tamb
Tmin. < Tamb < Tmax.
Vic = ±6V to ±4V, Tamb
Tmin. < Tamb < Tmax.
No load, Vout = 0
90
70
70
50
108
88
11
CMR Common Mode Rejection Ratio
dB
SVR
ICC
Supply Voltage Rejection Ratio
Total Supply Current per Operator
dB
15
-4
mA
DYNAMIC PERFORMANCE
VOH
I
I
out = 160mA, RL to GND
out = 160mA, RL to GND
High Level Output Voltage
4
4.5
V
V
VOL
Low Level Output Voltage
-4.5
Vout = 7V peak
RL = 25Ω, Tamb
6500
5000
11000
130
AVD
Large Signal Voltage Gain
Gain Bandwidth Product
V/V
Tmin. < Tamb < Tmax.
A
VCL = +7, f = 20MHz
RL = 100Ω
VCL = +7, RL = 50Ω
GBP
MHz
A
SR
Iout
Slew Rate
23
40
V/µs
Output Short Circuit Current
±240
mA
Vid = ±1V, Tamb
Tmin. < Tamb < Tmax.
RL = 25Ω//15pF
RL = 25Ω//15pF
±160
±140
Isink
Isource
Output Current
mA
Phase Margin at AVCL = 14dB
Phase Margin at AVCL = 6dB
ΦM14
ΦM6
60
40
°
°
NOISE AND DISTORTION
en
Equivalent Input Noise Voltage
f = 100kHz
3.2
1.5
nV/√Hz
pA/√Hz
in
Equivalent Input Noise Current
Total Harmonic Distorsion
f = 100kHz
Vout = 4Vpp, f = 100kHz
AVCL = -10
THD
IM2-10
IM3-10
-69
-77
-77
dB
RL = 25Ω//15pF
F1 = 80kHz, F2 = 70kHz
Vout = 8Vpp, AVCL = -10
Load = 25Ω//15pF
2nd Order Intermodulation Product
3rd Order Intermodulation Product
dBc
dBc
F1 = 80kHz, F2 = 70kHz
Vout = 8Vpp, AVCL = -10
Load = 25Ω//15pF
3/10
TS635
INTERMODULATION DISTORTION
The curves shown below are the measurements results of a single operator wired as an adder with a gain
of 15dB.
The operational amplifier is supplied by a symmetric ±6V and is loaded with 25Ω.
Two synthesizers (Rhode & Schwartz SME) generate two frequencies (tones) (70 & 80kHz ; 180 &
280kHz).
An HP3585 spectrum analyzer measures the spurious level at different frequencies.
The curves are traced for different output levels (the value in the X ax is the value of each tone).
The output levels of the two tones are the same.
The generators and spectrum analyzer are phase locked to enhance measurement precision.
3rd ORDER INTERMODULATION
Gain=15dB, Vcc=±6V, RL=25Ω, 2 tones 70kHz/
80kHz
3rd ORDER INTERMODULATION
Gain=15dB, Vcc=±6V, RL=25Ω, 2 tones 180kHz/
280kHz
0
-10
-20
-30
-40
0
-10
-20
-30
-40
90kHz
-50
-50
80kHz
-60
230kHz
-60
380kHz
-70
-70
-80
-80
640kHz
60kHz
-90
-90
740kHz
220kHz
-100
-100
1
1,5
2
2,5
3
3,5
4
4,5
1
1,5
2
2,5
3
3,5
4
4,5
Vout peak (V)
Vout peak (V)
4/10
TS635
Closed Loop Gain and Phase vs. Frequency
Closed Loop Gain and Phase vs. Frequency
Gain=+2, Vcc=±6V, RL=25Ω
Gain=+6, Vcc=±6V, RL=25Ω
10
0
200
20
200
100
0
Gain
Gain
15
100
0
10
5
Phase
0
Phase
-10
-20
-30
-5
-10
-15
-20
-100
-200
-100
-200
10kHz
100kHz
1MHz
10MHz
100MHz
10kHz
100kHz
1MHz
10MHz
100MHz
Frequency
Frequency
Closed Loop Gain and Phase vs. Frequency
Equivalent Input Voltage Noise
Gain=+11, Vcc=±6V, RL=25Ω
Gain=+100, Vcc=±6V, no load
30
20
200
20
15
10
5
Gain
+
_
100
0
10
10k
Phase
100
0
-10
-20
-30
-100
-200
0
100Hz
1kHz
10kHz
100kHz
1MHz
10kHz
100kHz
1MHz
10MHz
100MHz
Frequency
Frequency
Maximum Output Swing
Channel Separation (Xtalk) vs. Frequency
Vcc=±6V, RL=25Ω
XTalk=20Log(V2/V1), Vcc=±6V, RL=25Ω
-20
5
4
3
2
VIN
+
49.9Ω
output
_
V1
-30
-40
-50
-60
-70
-80
k
1
Ω
100Ω
100Ω
25Ω
input
1
+
49.9Ω
0
_
V2
-1
-2
-3
-4
-5
1kΩ
25Ω
0
2
4
6
Time (µs)
8
10
100kHz
1MHz
10MHz
10kHz
Frequency
5/10
TS635
THE TS635 AS LINE DRIVER ON ADSL LINE
INTERFACE. SINGLE SUPPLY
IMPLEMENTATION WITH PASSIVE OR ACTIVE
IMPEDANCE MATCHING.
namic range between 0 and +12 V. Several op-
tions are possible to provide this bias supply (such
as a virtual ground using an operational amplifier),
such as a two-resistance divider which is the
cheapest solution. A high resistance value is re-
quired to limit the current consumption. On the
other hand, the current must be high enough to
bias the inverting input of the TS635. If we consid-
er this bias current (5µA) as the 1% of the current
through the resistance divider (500µA) to keep a
stable mid supply, two 47kΩ resistances can be
used.
THE LINE INTERFACE - ADSL Remote
Terminal (RT):
The Figure1 shows a typical analog line interface
used for ADSL service. On this note, the accent
will be made on the emission path. The TS635 is
used as a dual line driver for the upstream signal.
The input provides two high pass filters with a
break frequency of about 1.6kHz which is neces-
sary to remove the DC component of the input sig-
nal. To avoid DC current flowing in the primary of
the transformer, an output capacitor is used. The
this case the load impedance is 25Ω for each driv-
er.
Figure 1 : Typical ADSL Line Interface
high output
current
ASCOT ADSL
Chip-Set
upstream
LP filter
emission
(analog)
impedance
matching
TS635
Line Driver
HYBRID
CIRCUIT
ST70135
ST70134
For the ADSL upstream path necessary to avoid
any distortion. In this simple non-inverting amplifi-
cation configuration, it will be easy to implement a
Sallen-Key lowpass filter by using the TS635. For
ADSL over POTS, a maximum frequency of
135kHz is reached. For ADSL over ISDN, the
maximum frequency will be 276kHz.
twisted-pair
telephone
line
downstream
VGA
reception
(analog)
TS636
Receiver
For the remote terminal it is required to create an
ADSL modem easy to plug in a PC. In such an ap-
plication, the driver should be implemented with a
+12 volts single power supply. This +12V supply is
available on PCI connector of purchase.
The Figure 2 shows a single +12V supply circuit
that uses the TS635 as a remote terminal trans-
mitter in differential mode.
INCREASING THE LINE LEVEL BY USING AN
ACTIVE IMPEDANCE MATCHING
With passive matching, the output signal ampli-
tude of the driver must be twice the amplitude on
the load. To go beyond this limitation an active
maching impedance can be used. With this tech-
nique it is possible to keep good impedance
matching with an amplitude on the load higher
than the half of the ouput driver amplitude. This
concept is shown in Figure 3 for a differential line.
Figure 2 : TS635 as a differential line driver with
a +12V single supply
Figure 3 : TS635 as a differential line driver with
1µ
100n
an active impedance matching
+12V
10n
+
_
12.5
+12V
GND
R2
1k
1:2
Vi
Vi
47k
µ
1
Vo
Vo
1/2 R1
Hybrid
100n
&
Vcc+
GND
Vcc/2
10n
+
_
Rs1
25Ω
100Ω
Transformer
1/2 R1
Vcc+
10µ
100n
1k
47k
R2
R3
Vo°
1:n
Vi
Vi
R3
Vo
1k
GND
+12V
+
12.5
1/2 R1
Hybrid
&
Transformer
RL
_
100Ω
Vcc/2
R5
GND
1/2 R1
100n
10µ
100n
Vo
Vo°
Rs2
R4
Vcc+
1k
GND
+
The driver is biased with a mid supply (nominaly
+6V), in order to maintain the DC component of
the signal at +6V. This allows the maximum dy-
_
GND
100n
6/10
TS635
Component calculation:
By identification of both equations (2) and (3), the
Let us consider the equivalent circuit for a single
ended configuration, Figure 4.
synthesized impedance is, with Rs1=Rs2=Rs:
Rs
----------------
Ro =
,(4 )
R2
------
Figure 4 : Single ended equivalent circuit
1 –
R3
Figure 5 : Equivalent schematic. Ro is the syn-
+
thesized impedance
Rs1
Vi
_
Vo°
Vo
R2
Iout
Ro
-1
R3
1/2
R1
1/2
RL
Vi.Gi
1/2RL
Let us consider the unloaded system. Assuming
the currents through R1, R2 and R3
as respectively:
2Vi (Vi – Vo°)
(Vi + Vo)
--------- --------------------------
-----------------------
and
,
R1
R2
R3
Unlike the level Vo° required for a passive imped-
ance, Vo° will be smaller than 2Vo in our case. Let
us write Vo°=kVo with k the matching factor vary-
ing between 1 and 2. Assuming that the current
through R3 is negligeable, it comes the following
resistance divider:
As Vo° equals Vo without load, the gain in this
case becomes :
2 R 2 R 2
---------- ------
1 +
+
Vo(noload)
R 1 R 3
----------------------------------
------------------------------
G =
=
Vi
R2
------
1 –
R3
kVoRL
---------------------------
Ro =
The gain, for the loaded system will be (1):
RL + 2Rs1
2 R 2 R 2
After choosing the k factor, Rs will equal to
1/2RL(k-1).
A good impedance matching assumes:
---------- ------
1 +
+
Vo(withload)
1
2
R 1 R 3
------------------------------------
-- ----------------------------------
,(1 )
GL =
=
Vi
R2
R3
------
1 –
1
--
Ro = RL,(5)
As shown in Figure 5, this system is an ideal gen-
erator with a synthesized impedance as the inter-
nal impedance of the system. From this, the out-
put voltage becomes:
2
From (4) and (5) it becomes:
R2
R3
2 Rs
RL
------
---------
= 1 –
,(6 )
Vo = (ViG) – (RoIout),(2)
By fixing an arbitrary value for R2, (6) gives:
with Ro the synthesized impedance and Iout the
output current. On the other hand Vo can be ex-
pressed as:
R2
-------------------
R3 =
2Rs
---------
1 –
RL
2R2 R 2
---------- ------
Vi 1 +
+
Finally, the values of R2 and R3 allow us to extract
R1 from (1), and it comes:
R1 R 3
Rs1Iout
---------------------------------------------- ---------------------
,(3 )
Vo =
–
R2
R3
R2
------
------
1 –
1 –
2 R 2
R3
---------------------------------------------------------
R 1 =
,(7 )
R2
R2
------
------
GL – 1 –
2 1 –
R3
R3
with GL the required gain.
GL (gain for the
loaded system)
GL is fixed for the application requirements
GL=Vo/Vi=0.5(1+2R2/R1+R2/R3)/(1-R2/R3)
R1
2R2/[2(1-R2/R3)GL-1-R2/R3]
Abritrary fixed
R2 (=R4)
R3 (=R5)
Rs
R2/(1-Rs/0.5RL)
0.5RL(k-1)
7/10
TS635
CAPABILITIES
MEASUREMENT OF THE POWER
CONSUMPTION
The table below shows the calculated compo-
nents for different values of k. In this case
R2=1000Ω and the gain=16dB. The last column
displays the maximum amplitude level on the line
regarding the TS635 maximum output capabilities
(18Vpp diff.) and a 1:2 line transformer ratio.
Conditions:
Power Supply: 12V
Passive impedance matching
Transformer turns ratio: 2
Maximun level required on the line: 12.4Vpp
Maximum output level of the driver: 12.4Vpp
Crest factor: 5.3 (Vp/Vrms)
The TS635 power consumption during emission
on 900 and 4550 meter twisted pair telephone
lines: 360mW
Active matching
TS635 Output
Level to get
12.4Vpp on
the line
Maximum
Line level
(Vpp diff)
R1
(Ω)
R3
(Ω)
Rs
(Ω)
k
(Vpp diff)
1.3
1.4
1.5
1.6
1.7
820 1500 3.9
490 1600 5.1
360 2200 6.2
270 2400 7.5
240 3300 9.1
Passive matching
8
27.5
25.7
25.3
23.7
22.3
18
8.7
9.3
9.9
10.5
12.4
8/10
TS635
PACKAGE MECHANICAL DATA
8 PINS - PLASTIC MICROPACKAGE (SO)
Millimeters
Dim.
Inches
Typ.
Min.
Typ.
Max.
Min.
Max.
A
a1
a2
a3
b
1.75
0.25
1.65
0.85
0.48
0.25
0.5
0.069
0.010
0.065
0.033
0.019
0.010
0.020
0.1
0.004
0.65
0.35
0.19
0.25
0.026
0.014
0.007
0.010
b1
C
c1
D
45° (typ.)
4.8
5.8
5.0
6.2
0.189
0.228
0.197
0.244
E
e
1.27
3.81
0.050
0.150
e3
F
3.8
0.4
4.0
1.27
0.6
0.150
0.016
0.157
0.050
0.024
L
M
S
8° (max.)
9/10
TS635
PACKAGE MECHANICAL DATA
8 PINS - PLASTIC MICROPACKAGE (SO Exposed-Pad)
Millimeters
Dim.
Inches
Typ.
Min.
Typ.
Max.
Min.
Max.
A
A1
A2
B
1.350
0.000
1.100
0.330
0.190
4.800
3.800
1.750
0.250
1.650
0.510
0.250
5.000
4.000
0.053
0.001
0.043
0.013
0.007
0.189
0.150
0.069
0.010
0.065
0.020
0.010
0.197
0.157
C
D
E
e
1.270
0.050
H
5.800
0.250
0.400
0d
6.200
0.500
1.270
8d
0.228
0.010
0.016
0d
0.244
0.020
0.050
8d
h
L
k
ddd
0.100
0.004
Information furnished is believed to be accurate and reliable. However, STMicroelectronics assumes no responsibility for the
consequences of use of such information nor for any infringement of patents or other rights of third parties which may result from
its use. No license is granted by implication or otherwise under any patent or patent rights of STMicroelectronics. Specifications
mentioned in this publication are subject to change without notice. This publication supersedes and replaces all information
previously supplied. STMicroelectronics products are not authorized for use as critical components in life support devices or
systems without express written approval of STMicroelectronics.
The ST logo is a registered trademark of STMicroelectronics
© 2002 STMicroelectronics - All Rights Reserved
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