U210B1 [TEMIC]
Phase Control Circuit Load Current Feedback Applications; 相位控制电路负载电流反馈应用
| 型号： | U210B1 |
| 厂家： | 
TEMIC SEMICONDUCTORS |
| 描述： | Phase Control Circuit Load Current Feedback Applications |
| 文件： | 总12页 (文件大小：156K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
U210B1
Phase Control Circuit–Load Current Feedback Applications
Description
The interated circuit, U210B1, is designed as a phase- and soft-start functions. The voltage obtained due to load
control circuit for load-current feedback application in current proportionality, can be used according to the
bipolar technology. To realize motor control systems, it application i.e., load-current compensation or load-
has integrated load current detection, voltage monitoring current regulation.
Features
Externally controlled integrated amplifier
Internal supply voltage monitoring
Temperature constant reference source
Current requirement ≤ 3 mA
Variable soft start
Automatic retriggering
Voltage and current synchronization
Triggering pulse typ. 125 mA
Package: DIP14
14
1
4
Output
pulse
Voltage
detector
Current
detector
Automatic
retriggering
5
6
Control
amplifier
8
7
+
–
Phase
control unit
= f (V12)
3
2
–V
Supply
voltage
S
GND
limitation
13
Reference
voltage
Voltage
monitoring
Load
current
Soft start
detection
12
11
9
10
95 10686
Figure 1. Block diagram
TELEFUNKEN Semiconductors
1 (12)
Rev. A1, 28-May-96
U210B1
Figure 2. Block diagram with external circuitry Open loop control with load current compensation
2 (12)
TELEFUNKEN Semiconductors
Rev. A1, 28-May-96
U210B1
Description
When the potential on Pin 6 reaches the nominal value
predetermined at Pin 9, then a trigger pulse is generated
Mains Supply
The U210B1 is fitted with voltage limiting and can there-
fore be supplied directly from the mains. The supply
voltage between Pin 2 (+pol/ ) and Pin 3 builds up
whose width t is determined by the value of C (the value
p
2
of C and hence the pulse width can be evaluated by
2
assuming 8 s/nF). At the same time, a latch is set, so that
as long as the automatic retriggering has not been
activated, then no more pulses can be generated in that
half cycle.
across D and R and is smoothed by C . The vaIue of the
1
1
1
series resistance can be approximated using:
V –V
M
S
R =
1
The current sensor on Pin 1 ensures that, for operation
with inductive loads, no pulse will be generated in a new
half cycle as long as current from the previous half cycle
is still flowing in the opposite direction to the supply volt-
age at that instant. This makes sure that “Gaps” in the load
current are prevented.
2 I
S
Further information regarding the design of the mains
supply can be found in the data sheets in the appendix.
The reference voltage source on Pin 13 of typ. –8.9 V is
derived from the supply voltage. It represents the refer-
ence level of the control unit.
The control signal on Pin 9 can be in the range 0 V to –7 V
(reference point Pin 2).
Operation using an externally stabiIised dc voltage is not
recommended.
If V = –7 V then the phase angle is at maximum =
9
max
If the supply cannot be taken directly from the mains be-
i .e. the current flow angle is a minimum. The minimum
phase angle is when V = V .
cause the power dissipation in R would be too large, then
1
min
9
2
the circuit shown in the following figure 3 should be
employed.
Voltage Monitoring
~
As the voltage is built up, uncontrolled output pulses are
avoided by internal voltage surveillance. At the same
time, all of the latches in the circuit (phase control, soft
start) are reset and the soft-start capacitor is short cir-
cuited. Used with a switching hysteresis of 300 mV, this
system guarantees defined start-up behaviour each time
the supply voltage is switched on or after short interrup-
tions of the mains supply.
24 V~
1
2
3
4
5
C
1
Soft-Start
R
1
95 10362
As soon as the supply voltage builds up (t ), the integrated
1
soft-start is initiated. The figure below shows the
behavior of the voltage across the soft-start capacitor and
is identical with the voltage on the phase control input on
Pin 9. This behaviour allows a gentle start-up for the
motor.
Figure 3. Supply voltage for high current requirements
Phase Control
The function of the phase control is largely identical to
that of the well known component TEA1007. The phase
angle of the trigger pulse is derived by comparing the C is first charged with typ. 30 A. The charging current
4
ramp voltage, which is mains synchronized by the voltage then increases as the voltage across C increases giving a
4
detector, with the set value on the control input Pin 9. The progressively rising charging function with more and
slope of the ramp is determined by C and its charging more strongly accelerates the motor with increasing rota-
2
current. The charging current can be varied using R on tional speed. The charging function determines the
2
Pin 5. The maximum phase angle
can also be acceleration up to the set point. The charging current can
have a maximum value of 85 A.
max
adjusted using R .
2
TELEFUNKEN Semiconductors
3 (12)
Rev. A1, 28-May-96
U210B1
96 11565
Pulse Output Stage
V
10
The pulse output stage is short circuit protected and can
typically deliver currents of 125 mA. For the design of
V
9
smaller triggering currents, the function I = f (R ) has
GT
GT
been given in the data sheets in the appendix. In contrast
to the TEA1007, the pulse output stage of the U210B1 has
no gate bypass resistor.
Automatic Retriggering
The automatic retriggering prevents half cycles without
current flow, even if the triac is turned off earlier e.g., due
to not exactly centred collector (brush lifter) or in the
event of unsuccessful triggering. After a time lapse of
t
t
1
t
2
t
pp
= 4.5 t is generated another triggering pulse which is
p
repeated until either the triac fires or the half cycle
finishes.
t
tot
General Hints and Explanation of Terms
To ensure safe and trouble-free operation, the following
points should be taken into consideration when circuits
are being constructed or in the design of printed boards.
Figure 4. Soft–start
t
= build-up of supply voltage
= run-up time
= total start-up time to required speed
1
2
The connecting lines from C to Pin 6 and Pin 2 should
be as short as possible, and the connection to Pin 2
should not carry any additional high current such as
2
t
t
tot
the load current. When selecting C , a low tempera-
ture coefficient is desirable.
2
Control Amplifier
95 10716
The integrated control amplifier with differential input
has a bipolar current output, with typically ±110 A at
Pin 9 and a transmittance of typ. 1000 A/V. The amplifi-
cation and frequency response are determined by external
circuit. For operation as a power control, it should be con-
nected with Pin 7. Phase angle of the firing pulse can be
adjusted by using the voltage at Pin 8. An internal limiting
circuit prevents the voltage on Pin 9 becoming more
V
Mains
Supply
/2
3/2
2
V
GT
Trigger
Pulse
t
p
negative than V + 1 V.
t
pp
= 4.5 t
p
13
V
Load Current Detection, Figure 2
L
Load
Voltage
Voltage drop across R , dependent of load current, gener-
8
ates an input-current at Pin 11 limited by R . Proportional
5
output current of 0.44 x I (CTR) is available at Pin 12.
11
It is proportional with respect to phase and amplitude of
load current.
I
L
Load
Current
Capacitor C integrates the current whereas resistor R
3
7
evaluates it. The voltage obtained due to load current
proportionality, can be used according to the application
i.e., load current compensation or load current regulation.
Figure 5. Explanation of terms in phase relationship
4 (12)
TELEFUNKEN Semiconductors
Rev. A1, 28-May-96
U210B1
Absolute Maximum Ratings
Reference point Pin 2, unless otherwise specified
Parameters
Symbol
–I
Value
30
Unit
mA
Current requirement
Pin 3
S
–i
s
100
t ≤ 10 s
Synchronisation current
Pin 1
Pin 14
Pin 1
–I
5
5
35
35
mA
sync.I
–I
sync.V
t ≤ 10 s
t ≤ 10 s
–i
I
Pin 14
i
v
Load current monitoring
Input current
Pin 11
Pin 11
–I
–I
2
5
mA
V
A
mA
I
t ≤ 10 s
I
Phase control
Input voltage
Input current
Pin 9
Pin 9
Pin 5
–V
I
–I
0 to 7
500
1
I
I
I
Soft–start
Input voltage
Pulse output
Reverse voltage
Amplifier
Pin 10
Pin 4
–V
V
to 0
V
V
I
13
V
o
V to 5
S
Input voltage
Pin 8
Pin 7
V
–V
0 to V
S
I
V
13
to 0
V
I
Reference voltage source
Output current
Storage temperature range
Junction temperature
Pin 13
I
7.5
–40 to +125
125
mA
°C
°C
o
T
stg
T
j
Ambient temperature range
T
amb
–10 to +100
°C
Thermal Resistance
Parameters
Symbol
R
thJA
Value
120
Unit
K/W
Junction ambient
DIP14
Electrical Characteristics
–V = 13 V, T
= 25°C, reference point Pin 2, unless otherwise specified
s
amb
Parameters
Supply voltage for mains
operations
Test Conditions / Pins
Pin 3
Symbol
Min.
13.0
Typ.
Max.
V
Limit
Unit
V
–V
S
Supply voltage limitation
–I = 3 mA
–I = 30 mA
S
Pin 3
–V
14.6
14.7
16.6
16.8
V
S
S
DC supply current
Reference voltage source
–V =13 V
Pin 3
Pin 13
–I
1.2
8.6
8.3
2.5
8.9
3.0
9.2
9.1
mA
V
S
S
–I = 10 A
–V
L
Ref
–I = 5 mA
L
Temperature coefficient
Voltage monitoring
Turn-on threshold
Pin 13 –TC
0.5
mV/K
VRef
Pin 3
Pin 3
–V
11.2
10.9
13.0
V
V
SON
Turn-off threshold
–V
9.9
SOFF
TELEFUNKEN Semiconductors
5 (12)
Rev. A1, 28-May-96
U210B1
Parameters
Test Conditions / Pins
Symbol
Min.
Typ.
Max.
Unit
mA
V
Phase control currents
Current synchronization
Voltage synchronization
Voltage limitation
Pin 1
Pin 14
I
0.35
0.35
8.0
8.0
3.5
3.5
9.5
9.5
sync.I
I
sync.V
±I = 5 mA
Pin 1
V
I
V
I
8.9
8.9
S
Pin 14
Reference ramp, figure 6
Load current
I = f(R )
Figure 6
6
F
R = 1 K ... 820 K Pin 6
I
1
1.06
20
1.18
A
V
mV/K
f
6
R –reference voltage
Temperature coefficient
Pulse output, figure 11
Output pulse current
Reverse current
Output pulse width
Automatic retriggering
Repetition rate
≥ 180 °
Pin5,3
Pin 5
V
TC
1.13
0.5
Ref
V Ref
R
= 0, V =1.2 V Pin 4
I
o
100
125
0.01
80
150
3.0
mA
A
s
GT
GT
Pin 4
Pin4,2
I
or
C = 10 nF
t
p
Pin 4
t
pp
3
4.5
6
t
p
Amplifier
Common mode voltage
range
Input bias current
Input offset voltage
Output current
Pin7,8
V
V
–1
1
V
7,8
13
Pin 8
Pin7,8
Pin 9
I
0.01
13
110
120
A
mV
A
IB
V
–I
+I
Y
IO
Figure 9
= f(V
75
88
145
165
O
O
Short circuit forward trans-
mittance
I
)
Pin 9
1000
A/V
12
10-11
f
Soft-start, figures 7, 8
Starting current
Final current
Discharge current, restart
pulse
Pin 10
V
V
= V
= –0.5 V
I
I
–I
20
50
0.5
30
85
3
50
130
10
A
A
mA
10
13
O
O
10
O
Load current detection, figure 10
Pin 11
Input current voltage
I
I
0
300
500
308
A
A
I
V = 300 mV, R = 1 K
I
1
I
Input offset voltage
Output open current
Output current
V
I
–8
1.9
0
5.5
mV
A
IO
O
V = 0 V, R = 1 K Pin 12
I
1
V = 300 mV, R = 1 K
I
1
V
= V
= 150 A
= 300 A
Pin 12
Pin 12/11
Pin 12/11
I
120
127
0.44 ± 5%
0.42 ± 6%
134
A
12
13
O
I
CTR
TC
12
Current transfer ratio
I
12
I12
I11
CTR
0
Temperature coefficient of
current transfer ratio
Pin 12/11
0.2
/ /K
00
6 (12)
TELEFUNKEN Semiconductors
Rev. A1, 28-May-96
U210B1
240
200
160
Phase Control
Reference Point Pin 2
100
50
Control Amplifier
10nF
4.7nF
2.2nF
0
120
80
0
–50
–100
C
=1.5nF
0.8
/t
Reference Point Pin 13
300
–300 –200 –100
0
100
200
1.0
0
0.2
0.4
0.6
)
96 11615
V
( V )
7–8
95 10302
R ( M
Figure 6.
Figure 9.
100
80
500
400
300
Reference Point for:
Soft Start
R =100
5
I
12
Pin 13, V Pin 2
R8
220
500
60
1k
40
20
0
200
100
0
2k
f/V-Converter non–active
Reference Point Pin 13
10
0
2
4
6
8
0.75
0
0.15
0.3
0.45
( V )
0.6
96 11616
V
( V )
10
95 10336
V
(R8)
Figure 7.
Figure 10.
10
8
100
80
Pulse Output
Soft Start
6
60
4
2
0
40
20
0
V
GT
= 0.8V
1.4V
f/V-Converter non–active
Reference Point Pin 13
1000
0
200
400
600
)
800
96 11617
t=f
95 10313
R
(
(C4)
GT
Figure 8.
Figure 11.
TELEFUNKEN Semiconductors
7 (12)
Rev. A1, 28-May-96
U210B1
50
40
30
Design Calculations for Mains Supply
The following equations can be used for the evaluation of
Mains Supply
the series resistor R for worst case conditions:
1
VMmin – VSmax
VM – VSmin
2 ISmax
R1max
0.85
R1min
2 Itot
20
10
2
(VMmax – VSmin
2 R1
)
P(R1max)
where:
0
0
V
VS
= Mains voltage, 230 V
= Supply voltage on Pin 3
M
16
40
15
4
8
12
95 10315
I
( mA )
I
= Total DC current requirement of the circuit
= I + I + I
tot
tot
Figure 12.
Smax
p
x
6
5
4
3
2
1
0
I
I
= Current requirement of the IC in mA
= Average current requirement of the triggering
pulses
= Current requirement of other peripheral
components
Smax
p
Mains Supply
I
x
R can be easily evaluated from the diagrams figures 12
1
to 14.
0
10
20
30
95 10316
R ( k
)
1
Figure 13.
6
5
4
3
2
1
0
Mains Supply
0
3
6
9
12
95 10317
I
tot
( mA )
Figure 14.
8 (12)
TELEFUNKEN Semiconductors
Rev. A1, 28-May-96
U210B1
Applications
In contrast to simple speed controller, the circuits shown The integrated load current proportional signal at C
3
in figures 15 and 16, react to the load dependent speed effects in the same direction on the control input as the set
drop in which the magnitude of the load current acts on point i.e., by the increase of load current follows an auto-
the speed compensation.
matic increase of manipulated set point, so that a
compensation of speed falls.
For this purpose, the load current is measured by shunt Compensation arrangement is influenced with resistance
resistor R . The voltage drop generates a current at Pin 11 values i.e. R (= 100 to 5 k ) and R (= 10 k to 150 k )
8
5
7
dependent of R , which reflects in the specified current at whereas the higher effect is achieved by increasing the
5
the output of Pin 12.
value of R and decreasing R . Influence of compensation
7 5
can be increased up to the value where the drive system
(motor) starts to oscillate.
Rated impedance of the output current at Pin 12 is repre-
sented through the coupling resistance R and the total Dimensioning in the applications are with the drill
7
impedance of the set point.
machine of 700 W power.
R
6
L
4.7 k
BC308B
T
220 nF
1
min
R
7
R
220 k
3
R
15
230 V~
10 k
C
3
22 k
max
C
4
N
M
D
1
15 F
10 V
1N4004
R
10
100 k
14
12
11
9
6
8
7
13
10
R
18 k
1.5 W
1
R
2 k
5
U210B
1
2
3
5
4
R
4
R
2
470 k
BTA
R
12
12–800
220 k
100
C
1
R
50 m
8
22 F
25 V
C
2
10 nF
Figure 15. Speed control with load current compensation
TELEFUNKEN Semiconductors
9 (12)
Rev. A1, 28-May-96
U210B1
R
6
L
6.8 k
min
R
15
C
R
3
3
R
7
220 k
max
230 V~
N
220 k
20 k
220 nF
C
4
M
D
1
R
10 k
R
11
10
1N4004
15 F
10 V
100 k
14
12
11
9
8
7
13
10
R
18 k
1.5 W
1
R
2 k
5
U210B
1
2
3
5
6
4
R
4
R
2
470 k
BTA
12–800
R
12
220 k
100
C
1
R
50 m
22 F
25 V
8
10 nF
C
2
Figure 16. Speed control with load current compensation
10 (12)
TELEFUNKEN Semiconductors
Rev. A1, 28-May-96
U210B1
L
R
3
R
7
R
6
2.2 k
220 k
330 k
C
3
230 V~
4.7 F
10 V
C
5
C
4
470 nF
C
6
min
N
D
1
Load
15 F
10 V
1N4004
P
1
0.1 F
8
100 k
max
14
12
11
9
6
13
10
R
9
47 k
R
1
R
5
U210B
18 k
1.5 W
2 k
1
2
3
5
4
7
R
4
R
2
470 k
BTA
12–800
R
12
220 k
100 k
C
1
R
50 m
22 F
25 V
8
C
10 nF
Figure 17. Load current regulation with soft start
Current regulation is achieved by the integrated opera- (actual value).
tional amplifier as P -controller (R , C , C ). Inverted
1
7
5
6
input (Pin 7) of the operational amplifier is directly con- Desired value is obtained with the help of potentiometer
nected at C with load current proportional test signal at Pin 8.
3
Dimensions in mm
Package: DIP14
94 9445
TELEFUNKEN Semiconductors
11 (12)
Rev. A1, 28-May-96
U210B1
Ozone Depleting Substances Policy Statement
It is the policy of TEMIC TELEFUNKEN microelectronic GmbH to
1. Meet all present and future national and international statutory requirements.
2. Regularly and continuously improve the performance of our products, processes, distribution and operating systems
with respect to their impact on the health and safety of our employees and the public, as well as their impact on
the environment.
It is particular concern to control or eliminate releases of those substances into the atmosphere which are known as
ozone depleting substances (ODSs).
The Montreal Protocol (1987) and its London Amendments (1990) intend to severely restrict the use of ODSs and
forbid their use within the next ten years. Various national and international initiatives are pressing for an earlier ban
on these substances.
TEMIC TELEFUNKEN microelectronic GmbH semiconductor division has been able to use its policy of
continuous improvements to eliminate the use of ODSs listed in the following documents.
1. Annex A, B and list of transitional substances of the Montreal Protocol and the London Amendments respectively
2. Class I and II ozone depleting substances in the Clean Air Act Amendments of 1990 by the Environmental
Protection Agency (EPA) in the USA
3. Council Decision 88/540/EEC and 91/690/EEC Annex A, B and C (transitional substances) respectively.
TEMIC can certify that our semiconductors are not manufactured with ozone depleting substances and do not contain
such substances.
We reserve the right to make changes to improve technical design and may do so without further notice.
Parameters can vary in different applications. All operating parameters must be validated for each customer
application by the customer. Should the buyer use TEMIC products for any unintended or unauthorized
application, the buyer shall indemnify TEMIC against all claims, costs, damages, and expenses, arising out of,
directly or indirectly, any claim of personal damage, injury or death associated with such unintended or
unauthorized use.
TEMIC TELEFUNKEN microelectronic GmbH, P.O.B. 3535, D-74025 Heilbronn, Germany
Telephone: 49 (0)7131 67 2831, Fax number: 49 (0)7131 67 2423
12 (12)
TELEFUNKEN Semiconductors
Rev. A1, 28-May-96
相关型号：
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