U211B2-B [TEMIC]
AC Motor Controller, BIPolar, PDIP18, DIP-18;
| 型号： | U211B2-B |
| 厂家： | 
TEMIC SEMICONDUCTORS |
| 描述： | AC Motor Controller, BIPolar, PDIP18, DIP-18 光电二极管 |
| 文件： | 总20页 (文件大小：321K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
U211B2/ B3
Phase Control Circuit - General Purpose Feedback
Description
The integrated circuit U211B2/ B3 is designed as a phase It has an integrated load limitation, tacho monitoring and
control circuit in bipolar technology with an internal fre- soft-start functions, etc. to realize sophisticated motor
quency-voltage converter. Furthermore, it has an internal control systems.
control amplifier which means it can be used for speed-
regulated motor applications.
Triggering pulse typ. 155 mA
Features
Voltage and current synchronization
Internal frequency-to-voltage converter
Internal supply-voltage monitoring
Externally-controlled integrated amplifier
Temperature reference source
Overload limitation with a “fold back” characteristic
Current requirement ≤ 3 mA
Optimized soft-start function
Tacho monitoring for shorted and open loop
Package:
DIP18 - U211B2,
SO16 - U211B3
Automatic retriggering switchable
17(16)
1(1)
5*)
4(4)
Automatic
retriggering
Voltage / Current
detector
Output
pulse
Control
amplifier
6(5)
7(6)
11(10)
10(9)
+
–
Phase
control unit
= f (V12)
3(3)
2(2)
–V
Supply
voltage
limitation
S
GND
Reference
voltage
14(13)
15(14)
16(15)
Load limitation
speed / time
controlled
Voltage
monitoring
Pulse-blocking
tacho
Frequency-
to-voltage
converter
controlled
current sink
Soft start
18*)
monitoring
–V
Ref
12(11)
13(12)
9(8)
8(7)
95 10360
Figure 1. Block diagram (Pins in brackets refer to SO16)
*) Pins 5 and 18 connected internally
TELEFUNKEN Semiconductors
1 (20)
Rev. A1, 29-May-96
U211B2/ B3
Figure 2. Speed control, automatic retriggering, load limiting, soft start
2 (20)
TELEFUNKEN Semiconductors
Rev. A1, 29-May-96
U211B2/ B3
Description
When the potential on Pin 7 reaches the nominal value
predetermined at Pin 12, then a trigger pulse is generated
Mains Supply
The U211B2 is fitted with voltage limiting and can
therefore be supplied directly from the mains. The supply
voltage between Pin 2 (+ pol/ ) and Pin 3 builds up
whose width t is determined by the value of C (the value
p
2
of C and hence the pulse width can be evaluated by
2
assuming 8 s/nF). At the same time, a latch is set, so that
as long as the automatic retriggering has not been
activated, then no more pulses can be generated in that
half cycle.
across D and R and is smoothed by C . The value of the
1
1
1
series resistance can be approximated using (see
figure 2):
VM – VS
R1
2 IS
The current sensor on Pin 1 ensures that, for operations
with inductive loads, no pulse will be generated in a new
half-cycle as long as a current from the previous half
cycle is still flowing in the opposite direction to the
supply voltage at that instant. This makes sure that “gaps”
in the load current are prevented.
Further information regarding the design of the mains
supply can be found in the data sheets in the appendix.
The reference voltage source on Pin 16 of typ. –8.9 V is
derived from the supply voltage and is used for
regulation.
Operation using an externally stabilised DC voltage is not
recommended.
The control signal on Pin 12 can be in the range 0 V to
–7 V (reference point Pin 2).
If the supply cannot be taken directly from the mains
because the power dissipation in R would be too large,
then the circuit shown in the following figure 3 should be
used.
1
If V = –7 V then the phase angle is at maximum = max
i.e., the current flow angle is a minimum. The phase angle
12
is minimum when V = V .
min
12
2
~
Voltage Monitoring
24 V~
As the voltage is built up, uncontrolled output pulses are
avoided by internal voltage surveillance. At the same
time, all of the latches in the circuit (phase control, load
limit regulation, soft start) are reset and the soft-start
capacitor is short circuited. Used with a switching
hysteresis of 300 mV, this system guarantees defined
start-up behavior each time the supply voltage is switched
on or after short interruptions of the mains supply.
1
2
3
4
5
C
1
R
1
95 10362
Figure 3. Supply voltage for high current requirements
Phase Control
Soft-Start
There is a general explanation in the data sheet,
TEA1007, on the common phase control function. The
phase angle of the trigger pulse is derived by comparing As soon as the supply voltage builds up (t ), the integrated
1
the ramp voltage (which is mains synchronized by the soft-start is initiated. The figure below shows the
voltage detector) with the set value on the control input behaviour of the voltage across the soft-start capacitor
Pin 12. The slope of the ramp is determined by C and its and is identical with the voltage on the phase control input
2
charging current. The charging current can be varied on Pin 12. This behaviour guarantees a gentle start-up for
using R on Pin 6. The maximum phase angle
can the motor and automatically ensures the optimum run-up
time.
2
max
also be adjusted using R .
2
TELEFUNKEN Semiconductors
3 (20)
Rev. A1, 29-May-96
U211B2/ B3
95 10272
The converter is based on the charge pumping principle.
With each negative half wave of the input signal, a
V
C3
quantity of charge determined by C is internally
5
V
amplified and then integrated by C at the converter
12
6
output on Pin 10. The conversion constant is determined
by C , its charge transfer voltage of V , R (Pin 10) and
5
ch
6
the internally adjusted charge transfer gain.
I10
Gi
8.3
I9
k = G
V
0
C
5
R
6
V
ch
i
t
The analog output voltage is given by
V = k
t
1
t
3
f
O
t
2
t
tot
The values of C and C must be such that for the highest
5
6
possible input frequency, the maximum output voltage
V does not exceed 6 V. While C is charging up, the R
i
Figure 4. Soft-start
O
5
on Pin 9 is .approx. 6.7 k . To obtain good linearity of the
f/V converter the time constant resulting from R and C
should be considerably less (1/5) than the time span of the
negative half-cycle for the highest possible input
frequency. The amount of remaining ripple on the output
t
= build-up of supply voltage
= charging of C to starting voltage
1
i
5
t
2
3
t + t = dead time
1
2
t
t
= run-up time
= total start-up time to required speed
3
tot
voltage on Pin 10 is dependent on C , C and the internal
5
6
charge amplification.
C is first charged up to the starting voltage V with
3
0
typical 45 A current (t ). By then reducing the charging
2
G
V
C
5
i
ch
current to approx. 4 A, the slope of the charging function
is substantially reduced so that the rotational speed of the
motor only slowly increases. The charging current then
∆V =
O
C
6
The ripple ∆V can be reduced by using larger values of
C . However, the increasing speed will then also be
reduced.
o
increases as the voltage across C increases giving a
3
6
progressively rising charging function which accelerates
the motor more and more strongly with increasing
rotational speed. The charging function determines the
acceleration up to the set-point. The charging current can
have a maximum value of 55 A.
The value of this capacitor should be chosen to fit the
particular control loop where it is going to be used.
Pulse Blocking
Frequency to Voltage Converter
The output of pulses can be blocked using Pin 18 (standby
operation) and the system reset via the voltage monitor if
≥ –1.25 V. After cycling through the switching point
hysteresis, the output is released when V ≤ –1.5 V
The internal frequency to voltage converter (f/V-
converter) generates a DC signal on Pin 10 which is
proportional to the rotational speed using an AC signal
from a tacho-generator or a light beam whose frequency
is in turn dependent on the rotational speed. The high
impedance input Pin 8, compares the tacho-voltage to a
switch-on threshold of typ. –100 mV. The switch-off
threshold is given with –50 mV. The hysteresis
guarantees very reliable operation even when relatively
simple tacho-generators are used. The tacho-frequency is
given by:
V
18
18
followed by a soft-start such as that after turn on.
Monitoring of the rotation can be carried out by
connecting an RC network to Pin 18. In the event of a
short or open circuit, the triac triggering pulses are cut off
by the time delay which is determined by R and C. The
capacitor C is discharged via an internal resistance
R = 2 k with each charge transfer process of the f/V
i
converter. If there are no more charge transfer processes
C is charged up via R until the switch-off threshold is
exceeded and the triac triggering pulses are cut off. For
operation without trigger pulse blocking or monitoring of
the rotation, Pins 18 and 16 must be connected together.
n
60
f
p (Hz)
where:
4 (20)
n = revolutions per minute
p = number of pulses per revolution
TELEFUNKEN Semiconductors
Rev. A1, 29-May-96
U211B2/ B3
(reference voltage Pin 16) then a latch is set and the load
limiting is turned on. A current source (sink) controlled
by the control voltage on Pin 15 now draws current from
Pin 12 and lowers the control voltage on Pin 12 so that the
C = 1 F
10 V
phase angle is increased to
.
max
18
17
16
15
The simultaneous reduction of the phase angle during
which current flows causes firstly: a reduction of the
rotational speed of the motor which can even drop to zero
if the angular momentum of the motor is excessively
R = 1 M
large, and secondly: a reduction of the potential on C
9
which in turn reduces the influence of the current sink on
Pin 12. The control voltage can then increase again and
bring down the phase angle. This cycle of action sets up
a “balanced condition” between the “current integral” on
Pin 15 and the control voltage on Pin 12.
1
2
3
4
95 10363
Figure 5. Operation delay
Apart from the amplitude of the load current and the time
during which current flows, the potential on Pin 12 and
hence the rotational speed also affects the function of the
load limiting. A current proportional to the potential on
Control Amplifier (Figure 2)
The integrated control amplifier with differential input
compares the set value (Pin 11) with the instantaneous
value on Pin 10 and generates a regulating voltage on the
output Pin 12 (together with the external circuitry on
Pin 12) which always tries to hold the actual voltage at the
value of the set voltages. The amplifier has a
transmittance of typically 1000 A/V and a bipolar
current source output on Pin 12 which operates with
typically ±110 A. The amplification and frequency
Pin 10 gives rise to a voltage drop across R , via Pin 14,
10
so that the current measured on Pin 14 is smaller than the
actual current through R .
8
This means that higher rotational speeds and higher
current amplitudes lead to the same current integral.
Therefore, at higher speeds, the power dissipation must
be greater than that at lower speeds before the internal
threshold voltage on Pin 15 is exceeded. The effect of
speed on the maximum power is determined by the
response are determined by R , C , C and R (can be left
7
7
8
11
out). For open loop operation, C , C , R , R , C , C and
4
5
6
7
7
8
resistor R and can therefore be adjusted to suit each
10
R
11
can be omitted. Pin 10 should be connected with
individual application.
Pin 12 and Pin 8 with Pin 2. The phase angle of the
triggering pulse can be adjusted using the voltage on
Pin 11. An internal limitation circuit prevents the voltage
If, after the load limiting has been turned on, the
momentum of the load sinks below the “o-momentum”
set using R , then V will be reduced. V can then in-
on Pin 12 from becoming more negative than V + 1 V.
16
10
15
12
crease again so that the phase angle is reduced. A smaller
phase angel corresponds to a larger momentum of the mo-
tor and hence the motor runs up - as long as this is allowed
by the load momentum. For an already rotating machine,
the effect of rotation on the measured “current integral”
ensures that the power dissipation is able to increase with
the rotational speed. the result is: a current controlled
accelleration run-up., which ends in a small peak of accel-
leraton when the set point is reached. The latch of the load
limiting is simultaneously reset. The speed of the motor
is then again under control and it is capable of carrying its
full load. The above mentioned peak of accelleration
depends upon the ripple of actual speed voltage. A large
amount of ripple also leads to a large peak of
accelleration.
Load Limitation
The load limitation, with standard circuitry, provides
absolute protection against overloading of the motor. the
function of the load limiting takes account of the fact that
motors operating at higher speeds can safely withstand
large power dissipations than at lower speeds due to the
increased action of the cooling fan. Similary, consider-
ations have been made for short term overloads for the
motor which are, in practice, often required. These
finctions are not damaging and can be tolerated.
In each positive half-cycle, the circuit measures via R
the load current on Pin 14 as a potential drop across R
and produces a current proportional to the voltage on
Pin 14. This current is available on Pin 15 and is
10
8
integrated by C . If, following high current amplitudes or The measuring resistor R should have a value which
9
8
a large phase angle for current flow, the voltage on C
ensures that the amplitude of the voltage across it does not
9
exceeds an internally set threshold of approx. 7.3 V exceed 600 mV.
TELEFUNKEN Semiconductors
5 (20)
Rev. A1, 29-May-96
U211B2/ B3
Design Hints
Practical trials are normally needed for the exact following table shows the effect of the circuitry on the
determination of the values of the relevant components in important parameters of the load limiting and summarises
the load limiting. To make this evaluation easier, the the general tendencies.
Parameters
Component affected
R
10
R
9
C
9
P
P
P
increases
increases
increases
n.e.
decreases
decreases
n.e.
n.e.
max
n.e.
min
/
n.e.
max min
t
t
decreases
increases
increases
increases
d
n.e.
r
P
P
– maximum continuous power dissipation
– power dissipation with no rotation
– operation delay time
P = f n
(n)
0
max
min
1
P = f n = 0
1
(n)
t
t
d
– recovery time
r
n.e
– no effect
Pulse Output Stage
General Hints and Explanation of Terms
To ensure safe and trouble-free operation, the following
points should be taken into consideration when circuits
are being constructed or in the design of printed circuit
boards.
The pulse output stage is short circuit protected and can
typically deliver currents of 125 mA. For the design of
smaller triggering currents, the function I = f(R ) has
GT
GT
been given in the data sheets in the appendix.
–
–
The connecting lines from C to Pin 7 and Pin 2
should be as short as possible: The connection to Pin 2
should not carry any additional high current such as
2
Automatic Retriggering
The variable automatic retriggering prevents half cycles
without current flow, even if the triac is turned off earlier
e.g. due to a collector which is not exactly centered (brush
lifter) or in the event of unsuccessful triggering. If it is
necessary, another triggering pulse is generated after a
time lapse which is determined by the repetition rate set
the load current. When selecting C ,
a low
2
temperature coefficient is desirable.
The common (earth) connections of the set-point
generator, the tacho-generator and the final
interference suppression capacitor C of the f/V
4
by resistance between Pin 5 and Pin 3 (R ). With the
converter should not carry load current.
5-3
maximum repetition rate (Pin 5 directly connected to
Pin 3), the next attempt to trigger comes after a pause of
–
–
The tacho-generator should be mounted without
influence by strong stray fields from the motor.
4.5 t and this is repeated until either the triac fires or the
p
The connections from R and C should be as short
10
5
half-cycle finishes. If Pin 5 is connected, then only one
trigger pulse per half-cycle is generated. Because the
as possible.
To achieve a high noise immunity, a maximum ramp
voltage of 6 V should be used.
value of R determines the charging current of C , any
5-3
2
repetition rate set using R is only valid for a fixed value
5-3
of C .
The typical resistance R can be calculated from I as
follows:
2
T(ms)
1.13(V)
6(V)
103
R (k )
C nF)
T = Period duration for mains frequency
(10 ms at 50 Hz)
C = Ramp capacitor, max. ramp voltage 6 V
and constant voltage drop at R = 1.13 V.
A 10% lower value of R (under worst case conditions)
is recommended.
6 (20)
TELEFUNKEN Semiconductors
Rev. A1, 29-May-96
U211B2/ B3
95 10716
V
Mains
Supply
/2
3/2
2
V
GT
Trigger
Pulse
t
p
t
pp
= 4.5 t
p
V
L
Load
Voltage
I
L
Load
Current
Figure 6. Explanation of terms in phase relationship
Design Calculations for Mains Supply
The following equations can be used for the evaluation of the series resistor R for worst case conditions:
1
VMmin – VSmax
2 Itot
VM – VSmin
2 ISmax
R1max
0.85
R1min
2
(VMmax – VSmin
)
P(R1max)
where:
2 R1
V
M
= Mains voltage
VS
= Supply voltage on Pin 3
= Total DC current requirement of the circuit
= I + I + I
I
tot
S
p
x
I
I
I
= Current requirement of the IC in mA
= Average current requirement of the triggering pulse
= Current requirement of other peripheral components
Smax
p
x
R can be easily evaluated from the figures 20 to 22.
1
TELEFUNKEN Semiconductors
7 (20)
Rev. A1, 29-May-96
U211B2/ B3
Absolute Maximum Ratings
Reference point Pin 2, unless otherwise specified
Parameters
Symbol
–I
Value
30
Unit
mA
Current requirement
Pin 3
S
–i
s
100
t ≤ 10 s
Synchronization current
Pin 1
Pin 17
Pin 1
I
5
5
35
35
mA
syncI
I
syncV
t
t
10 s
10 s
±i
I
±i
I
Pin 17
f/V converter
Pin 8
Input current
I
3
mA
I
±i
13
t
t
10 s
10 s
I
Load limiting
Pin 14
Limiting current, neg. half wave
I
5
35
1
mA
V
I
Input voltage
Pin 14
Pin 15
±V
i
–V
V
to 0
I
16
Phase control
Input voltage
Input current
Pin 12
Pin 12
Pin 6
–V
0 to 7
500
1
V
A
mA
I
±I
I
–I
I
Soft-start
Input voltage
Pulse output
Reverse voltage
Pulse blocking
Input voltage
Amplifier
Pin 13
Pin 4
–V
V
to 0
V
V
V
V
I
16
V
R
V to 5
S
Pin 18
–V
V
16
to 0
I
Input voltage
Pin 9 open
Pin 11
Pin 10
V
I
0 to V
S
–V
V
16
to 0
I
Reference voltage source
Output current
Storage temperature range
Junction temperature
Pin 16
I
7.5
–40 to +125
125
mA
°C
°C
o
T
stg
T
j
Ambient temperature range
T
amb
–10 to +100
°C
Thermal Resistance
Parameters
Symbol
Maximum
Unit
K/W
Junction ambient
DIP18
SO16 on p.c.
SO16 on ceramic
R
thJA
120
180
100
8 (20)
TELEFUNKEN Semiconductors
Rev. A1, 29-May-96
U211B2/ B3
Electrical Characteristics
–V = 13.0 V, T
= 25°C, reference point Pin 2, unless otherwise specified
S
amb
Parameters
Supply voltage for mains op-
eration
Test Conditions / Pins
Pin 3
Symbol
Min.
13.0
Typ.
Max.
V
Limit
Unit
V
–V
S
Supply voltage limitation
–I = 4 mA
–I = 30 mA
S
Pin 3
–V
–V
14.6
14.7
16.6
16.8
V
S
S
S
DC current requirement
Reference voltage source
–V = 13.0 V
Pin 3
Pin 16
I
–V
1.2
8.6
8.3
2.5
8.9
3.0
9.2
9.1
mA
V
S
S
–I = 10 A
L
Ref
–I = 5 mA
L
Temperature coefficient
Voltage monitoring
Turn-on threshold
Pin 16 –TC
0.5
mV/K
VRef
Pin 3 –V
11.2
9.9
13.0
10.9
V
V
SON
Turn-off threshold
Pin 3 –V
SOFF
Phase control currents
Synchronization current
Pin 1
0.35
0.35
1.4
2.0
2.0
1.8
mA
V
I
syncI
I
Pin 17
syncV
Voltage limitation
Reference ramp, figure 7
Charge current
1.6
I = 5 mA Pins 1 and 17
V
I
L
I = f (R );
7
6
R = 50 k to 1 M
Pin 7
Pins 6 and 3
Pin 6 TC
I
1
1.06
20
1.13
0.5
A
V
mV/K
6
7
R -reference voltage
Temperature coefficient
Pulse output, figure 18
Output pulse current
Reverse current
≥
°C
V
1.18
Ref
V Ref
Pin 4
= 0, V = 1.2 V
R
GT
I
o
100
155
0.01
80
190
3.0
mA
A
s
GT
I
or
Output pulse width
Amplifier
Cϕ = 10 nF
t
p
Common mode signal range
Input bias current
Input offset voltage
Output current
Pins 10 and 11
Pin 11
Pins 10 and 11
Pin 12
V ,
V
–1
1
V
A
mV
A
10 11
16
I
0.01
10
110
120
IO
V
10
–I
75
88
145
165
O
+I
O
Short circuit forward,
transmittance
Pulse blocking, tacho-monitoring
Logic-on
Logic-off
Input current
Figure 14
I
= f(V
)
Pin 12
Pin 18
Y
f
1000
A/V
V
12
10 -11
–V
3.7
1.5
1.25
0.3
TON
–V
1.0
1
TOFF
V
18
V
18
= V
= V
= 1.25 V
I
A
k
TOFF
16
I
14.5
1.5
Output resistance
R
O
6
10
TELEFUNKEN Semiconductors
9 (20)
Rev. A1, 29-May-96
U211B2/ B3
Parameters
Frequency to voltage converter
Input bias current
Test Conditions / Pins
Symbol
Min.
Typ.
0.6
Max.
2
Unit
A
Pin 8
I
IB
Input voltage limitation
Figure 13
I = –1 mA
–V
+V
660
7.25
750
8.05
mV
V
I
I
I = +1 mA
I
I
Turn-on threshold
Turn-off threshold
Charge amplifier
Discharge current
–V
100
50
150
mV
mV
TON
–V
20
TOFF
Figure 2
C = 1 nF,
Pin 9
I
0.5
mA
V
5
dis
Charge transfer voltage
Charge transfer gain
Conversion factor
Pins 9 to 16
Pins 9 and 10
V
G
i
6.50
7.5
6.70
8.3
6.90
9.0
ch
I /I
10
9
Figure 2
C = 1 nF, R = 100 k
K
5.5
0-6
1
mV/Hz
5
6
Output operating range
Linearity
Pins 10 to 16
V
O
V
%
Soft-start, figures 8, 9, 10, 11, 12 f/v-converter non-active
Starting current
Final current
V
13
V
13
= V V = V Pin 13
I
20
50
45
85
55
130
A
16,
8
2
O
= 0.5
Pin 13
f/v-converter active
Starting current
Final current
Discharge current
Automatic retriggering, figure 19
V
V
= V
= 0.5
Pin 13
I
I
2
30
0.5
4
55
3
7
80
10
A
A
mA
13
16
O
O
13
Restart pulse
Pin 13
Pin 5
Repetition rate
R
5-3
R
5-3
= 0
= 15 k
t
pp
3
4.5
20
6
t
p
Load limiting, figures 15, 16, 17
Pin 14
Operating voltage range
Offset current
Pin 14
Pin 14
V
–1.0
5
1.0
12
V
I
V
V
= V
= V via 1 k
I
10
14
16
O
A
2
Pin 15–16
Pin 14
= 300 mV Pin 15–16
Pin 15–16
0.1
90
1.0
120
140
7.7
Input current
Output current
Overload ON
V
V
= 4.5 V
I
60
110
7.05
10
I
I
14
O
V
7.4
V
TON
10 (20)
TELEFUNKEN Semiconductors
Rev. A1, 29-May-96
U211B2/ B3
240
200
160
10
8
Phase Control
Reference Point Pin 2
10nF 4.7nF
Soft Start
2.2nF
6
120
80
0
4
2
0
C
=1.5nF
/t
f/V-Converter Non Active
Reference Point Pin 16
1.0
10
10
0
0
0
0.2
0.4
0.6
)
0.8
95 10302
R
( M
95 10305
t=f
(C3)
Figure 7.
Figure 10.
100
80
10
8
Soft Start
Soft Start
f/V-Converter Active
Reference Point Pin 16
60
6
40
20
0
4
2
0
f/V-Converter Non Active
Reference Point Pin 16
2
4
6
8
95 10303
V
( V )
95 10306
t=f
(C3)
13
Figure 8.
Figure 11.
95 10307
10
8
100
80
Soft Start
Reference Point Pin 16
Soft Start
f/V-Converter Active
Reference Point Pin 16
6
60
4
2
0
40
20
0
t=f
(C3)
Motor Standstill ( Dead Time )
Motor in Action
2
4
6
8
95 10304
V
( V )
13
Figure 9.
Figure 12.
TELEFUNKEN Semiconductors
11 (20)
Rev. A1, 29-May-96
U211B2/ B3
500
200
150
100
50
f/V–Converter
250
Load Limit Control
Reference Point Pin 2
0
–250
–500
0
4
300
8
8
–10 –8
–6
–4
–2
0
2
0
0
0
2
4
6
95 10308
V ( V )
95 10311
V
(V)
10–16
8
Figure 13.
Figure 16.
250
200
150
Load current detection
100
Control Amplifier
50
0
100
50
0
–50
–100
I
=f ( V
)
15
Shunt
V
=V
10
16
Reference Point
for I = –4V
12
700
–300 –200 –100
0
100
( V )
200
100 200 300 400 500 600
( mV )
95 10309
V
95 10312
V
14–2
10–11
Figure 14.
Figure 17.
200
100
80
Load Limit Control
Pulse Output
150
100
50
60
40
20
0
1.4V
V
=0.8V
GT
0
1000
0
2
4
6
200
400
600
)
800
95 10310
V
( V )
95 10313
R
(
15–16
GT
Figure 15.
Figure 18.
12 (20)
TELEFUNKEN Semiconductors
Rev. A1, 29-May-96
U211B2/ B3
20
15
10
5
6
5
4
3
2
1
0
Automatic Retriggering
Mains Supply
0
30
40
0
6
12
18
24
0
10
20
30
95 10314
t
pp
/t
p
95 10316
R ( k
1
)
Figure 19.
Figure 21.
50
40
30
6
5
4
3
2
1
0
Mains Supply
Mains Supply
20
10
0
16
15
0
4
8
12
0
3
6
9
12
95 10315
I
tot
( mA )
95 10317
I
( mA )
tot
Figure 20.
Figure 22.
TELEFUNKEN Semiconductors
13 (20)
Rev. A1, 29-May-96
U211B2/ B3
Figure 23. Speed control, automatic retriggering, load switch-off, soft start
The switch-off level at maximum load shows in principle This function is effected by the thyristor (formed by T
1
the same speed dependency as the original version (see and T which ignites when the voltage at Pin 15 reaches
2)
figure 2), but when reaching the maximum load, the typ. 7.4 V (Reference point Pin 16). The circuit is thereby
motor is switched off completely.
switched into the “stand-by” over the release Pin 18.
14 (20)
TELEFUNKEN Semiconductors
Rev. A1, 29-May-96
U211B2/ B3
Figure 24. Speed control, automatic retriggering, load switch-off, soft-start
The maximum load regulation shows the principle in the at Pin 15 is lifted and kept by R over the internally
14
same speed dependency as the original version (see operating threshold whereby the maximum load
figure 2). When reaching the maximum load, the control regulation starts and adjusts the control unit constantly to
unit is turned to
flows. This function is effected by the thyristor, formed shows that the circuit is still in operation by a quiet
by T and T which ignites as soon as the voltage at Pin 15 buzzing noise.
, adjustable with R . Then only I
(I ), inspite of a reduced load current. The motor
max O
max
2
O
1
2
reaches ca. 6.8 V (Reference point Pin 16). The potential
TELEFUNKEN Semiconductors
15 (20)
Rev. A1, 29-May-96
U211B2/ B3
Figure 25. Speed control, automatic retriggering, load limiting, soft-start, tacho control
16 (20)
TELEFUNKEN Semiconductors
Rev. A1, 29-May-96
U211B2/ B3
Figure 26. Speed control with reflective opto coupler CNY70 as emitter
TELEFUNKEN Semiconductors
17 (20)
Rev. A1, 29-May-96
U211B2/ B3
Figure 27. Speed control, max. load control with reflective opto coupler CNY70 as emitter
18 (20)
TELEFUNKEN Semiconductors
Rev. A1, 29-May-96
U211B2/ B3
The circuit is designed as a speed control on the Instructions for adjusting:
reflection-coupled principle with 4 periods per revolution
In the initial adjustment of the phase-control circuit,
and a max. speed of 30.000 rpm. The separation of the
coupler from the rotating aperture should be 1 mm
approximately. In this experimental circuit, the power
supply for the coupler was provided externally because of
the relatively high current consumption.
R should be adjusted so that when R = 0 and R are
2
14
31
in min. position, the motor just turns.
The speed can now be adjusted as desired by means of
between the limits determined by R and R .
R
31
13
14
The switch-off power of the limit load control can be
set by R . The lower R , the higher the switch-off
9
9
power.
Dimensions in mm
Package: DIP18 – U211B2
94 8877
Package: SO16 – U211B3
94 8875
TELEFUNKEN Semiconductors
19 (20)
Rev. A1, 29-May-96
U211B2/ B3
Ozone Depleting Substances Policy Statement
It is the policy of TEMIC TELEFUNKEN microelectronic GmbH to
1. Meet all present and future national and international statutory requirements.
2. Regularly and continuously improve the performance of our products, processes, distribution and operating systems
with respect to their impact on the health and safety of our employees and the public, as well as their impact on
the environment.
It is particular concern to control or eliminate releases of those substances into the atmosphere which are known as
ozone depleting substances (ODSs).
The Montreal Protocol (1987) and its London Amendments (1990) intend to severely restrict the use of ODSs and
forbid their use within the next ten years. Various national and international initiatives are pressing for an earlier ban
on these substances.
TEMIC TELEFUNKEN microelectronic GmbH semiconductor division has been able to use its policy of
continuous improvements to eliminate the use of ODSs listed in the following documents.
1. Annex A, B and list of transitional substances of the Montreal Protocol and the London Amendments respectively
2. Class I and II ozone depleting substances in the Clean Air Act Amendments of 1990 by the Environmental
Protection Agency (EPA) in the USA
3. Council Decision 88/540/EEC and 91/690/EEC Annex A, B and C (transitional substances) respectively.
TEMIC can certify that our semiconductors are not manufactured with ozone depleting substances and do not contain
such substances.
We reserve the right to make changes to improve technical design and may do so without further notice.
Parameters can vary in different applications. All operating parameters must be validated for each customer
application by the customer. Should the buyer use TEMIC products for any unintended or unauthorized
application, the buyer shall indemnify TEMIC against all claims, costs, damages, and expenses, arising out of,
directly or indirectly, any claim of personal damage, injury or death associated with such unintended or
unauthorized use.
TEMIC TELEFUNKEN microelectronic GmbH, P.O.B. 3535, D-74025 Heilbronn, Germany
Telephone: 49 (0)7131 67 2831, Fax number: 49 (0)7131 67 2423
20 (20)
TELEFUNKEN Semiconductors
Rev. A1, 29-May-96
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