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INA282AIDR [TI]

High-Accuracy, Wide Common-Mode Range, Bi-Directional CURRENT SHUNT MONITOR Zero-Drift Series; 高精度，宽共模范围，双向电流分流监控器零漂移系列
INA282AIDR
型号： INA282AIDR
厂家： TEXAS INSTRUMENTS    TEXAS INSTRUMENTS
描述：

High-Accuracy, Wide Common-Mode Range, Bi-Directional CURRENT SHUNT MONITOR Zero-Drift Series
高精度，宽共模范围，双向电流分流监控器零漂移系列

运算放大器 放大器电路 光电二极管 监控 监视器 PC
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INA282, INA283  
INA284, INA285  
INA286  
www.ti.com  
SBOS485A –NOVEMBER 2009–REVISED JULY 2010  
High-Accuracy, Wide Common-Mode Range, Bi-Directional  
CURRENT SHUNT MONITOR  
Zerø-Drift Series  
Check for Samples: INA282, INA283, INA284, INA285, INA286  
1
FEATURES  
DESCRIPTION  
2
•
•
•
•
WIDE COMMON-MODE RANGE: –14V to 80V  
OFFSET VOLTAGE: ±20mV  
CMRR: 140dB  
The INA282 family, which includes the INA282,  
INA283, INA284, INA285, and INA286 devices, are  
voltage output current shunt monitors that can sense  
drops across shunts at common-mode voltages from  
–14V to +80V, independent of the supply voltage.  
The low offset of the Zerø-Drift architecture enables  
current sensing with maximum drops across the  
shunt as low as 10mV full-scale.  
ACCURACY:  
–
–
–
±1.4% Gain Error (Max)  
0.3mV/°C Offset Drift  
0.005%/°C Gain Drift (Max)  
These current shunt monitors operate from a single  
+2.7V to +18V supply, drawing a maximum of 900mA  
of supply current. They are specified over the  
extended operating temperature range of –40°C to  
+125°C, and offered in an SOIC-8 package.  
•
AVAILABLE GAINS:  
–
–
–
–
–
50V/V: INA282  
100V/V: INA286  
200V/V: INA283  
500V/V: INA284  
1000V/V: INA285  
Supply  
-14V to +80V  
+2.7V to +18V  
Load  
•
QUIESCENT CURRENT: 900mA (Max)  
+IN  
-IN  
V+  
APPLICATIONS  
•
•
•
•
TELECOM EQUIPMENT  
AUTOMOTIVE  
POWER MANAGEMENT  
SOLAR INVERTERS  
1
Æ2  
Æ2  
Æ1  
Æ2  
Æ2  
1
Æ1  
OUT  
ZerÆ-  
Drift  
Output  
GAIN  
PRODUCT  
50V/V  
INA282  
INA286  
INA283  
INA284  
INA285  
100V/V  
200V/V  
500V/V  
1000V/V  
33.3kW  
33.3kW  
REF2  
REF1  
GND  
1
Please be aware that an important notice concerning availability, standard warranty, and use in critical applications of Texas  
Instruments semiconductor products and disclaimers thereto appears at the end of this data sheet.  
2
All trademarks are the property of their respective owners.  
UNLESS OTHERWISE NOTED this document contains  
PRODUCTION DATA information current as of publication date.  
Products conform to specifications per the terms of Texas  
Instruments standard warranty. Production processing does not  
necessarily include testing of all parameters.  
Copyright © 2009–2010, Texas Instruments Incorporated  
INA282, INA283  
INA284, INA285  
INA286  
SBOS485A –NOVEMBER 2009–REVISED JULY 2010  
www.ti.com  
This integrated circuit can be damaged by ESD. Texas Instruments recommends that all integrated circuits be handled with  
appropriate precautions. Failure to observe proper handling and installation procedures can cause damage.  
ESD damage can range from subtle performance degradation to complete device failure. Precision integrated circuits may be more  
susceptible to damage because very small parametric changes could cause the device not to meet its published specifications.  
PACKAGE/ORDERING INFORMATION(1)  
PACKAGE  
DESIGNATOR  
PACKAGE  
MARKING  
PRODUCT  
INA282  
INA283(2)  
GAIN  
50V/V  
PACKAGE  
SOIC-8  
SOIC-8  
SOIC-8  
SOIC-8  
SOIC-8  
D
D
D
D
D
I282A  
I283A  
I284A  
I285A  
I286A  
200V/V  
500V/V  
1000V/V  
100V/V  
INA284  
INA285  
INA286  
(1) For the most current package and ordering information, see the Package Option Addendum located at the end of this data sheet, or  
refer to the device product folder at www.ti.com.  
(2) Shaded cells indicate a product preview device.  
ABSOLUTE MAXIMUM RATINGS(1)  
Over operating free-air temperature range, unless otherwise noted.  
INA282, INA283,  
INA284, INA285, INA286  
UNIT  
V
Supply Voltage  
Analog Inputs,  
+18  
(3)  
Differential (V+IN) – (V–IN  
)
–5 to +5  
V
(2)  
V+IN, V–IN  
Common-Mode  
–14 to +80  
V
Ref1, Ref2, Out  
GND–0.3 to (V+) + 0.3  
V
Input Current into Any Pin  
Storage Temperature  
Junction Temperature  
5
–65 to +150  
+150  
mA  
°C  
°C  
V
Human Body Model (HBM)  
Charged-Device Model (CDM)  
Machine Model (MM)  
3000  
ESD Ratings:  
1000  
V
200  
V
(1) Stresses above these ratings may cause permanent damage. Exposure to absolute maximum conditions for extended periods may  
degrade device reliability. These are stress ratings only, and functional operation of the device at these or any other conditions beyond  
those specified is not implied.  
(2) V+IN and V–IN are the voltages at the +IN and –IN pins, respectively.  
(3) Input voltages must not exceed common-mode rating.  
THERMAL INFORMATION  
INA282AID,  
INA283AID,  
INA284AID,  
INA285AID,  
THERMAL METRIC(1)  
UNITS  
INA286AID  
D
8
qJA  
Junction-to-ambient thermal resistance  
134.9  
72.9  
61.3  
18.9  
54.3  
n/a  
qJCtop  
qJB  
Junction-to-case (top) thermal resistance  
Junction-to-board thermal resistance  
°C/W  
yJT  
Junction-to-top characterization parameter  
Junction-to-board characterization parameter  
Junction-to-case (bottom) thermal resistance  
yJB  
qJCbot  
(1) For more information about traditional and new thermal metrics, see the IC Package Thermal Metrics application report, SPRA953.  
2
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Copyright © 2009–2010, Texas Instruments Incorporated  
Product Folder Link(s): INA282 INA283 INA284 INA285 INA286  
INA282, INA283  
INA284, INA285  
INA286  
www.ti.com  
SBOS485A –NOVEMBER 2009–REVISED JULY 2010  
ELECTRICAL CHARACTERISTICS  
Boldface limits apply over the specified temperature range, TA = –40°C to +125°C.  
At TA = +25°C, V+ = 5V, V+IN = 12V, VREF1 = VREF2 = 2.048V referenced to GND, and VSENSE = V+IN – V–IN, unless otherwise  
noted.  
INA282, INA283,  
INA284, INA285, INA286  
PARAMETER  
CONDITIONS  
VSENSE = 0mV  
MIN  
TYP  
MAX  
UNIT  
INPUT  
Offset Voltage, RTI(1)  
VOS  
dVOS/dT  
PSRR  
VCM  
±20  
±0.3  
3
±70  
mV  
mV/°C  
mV/V  
V
vs Temperature  
±1.5  
vs Power Supply  
VS = +2.7V to +18V, VSENSE = 0mV  
Common-Mode Input Range  
Common-Mode Rejection  
Input Bias Current per Pin(2)  
Input Offset Current  
Differential Input Impedance  
REFERENCE INPUTS  
Reference Input Gain  
Reference Input Voltage Range(3)  
Divider Accuracy(4)  
Reference Voltage Rejection Ratio  
INA282  
–14  
120  
80  
CMRR  
IB  
V+IN = –14V to +80V, VSENSE = 0mV  
VSENSE = 0mV  
140  
25  
1
dB  
mA  
IOS  
VSENSE = 0mV  
mA  
6
kΩ  
1
V/V  
V
0
VGND + 9  
±0.5  
±0.2  
%
VREF1 = VREF2 = 40mV to 9V, V+ = 18V  
±25  
0.055  
±13  
±75  
±30  
±25  
±10  
±45  
mV/V  
mV/V/°C  
mV/V  
vs Temperature  
INA283  
vs Temperature  
0.040  
±6  
mV/V/°C  
mV/V  
INA284  
vs Temperature  
0.015  
±4  
mV/V/°C  
mV/V  
INA285  
vs Temperature  
0.010  
±17  
mV/V/°C  
mV/V  
INA286  
vs Temperature  
0.040  
mV/V/°C  
GND + 0.5V ≤ VOUT ≤ (V+) – 0.5V;  
VREF1 = VREF2 = (V+)/2 for all devices  
GAIN(5)  
Gain  
G
INA282  
V+ = +5V  
V+ = +5V  
V+ = +12V  
V+ = +12V  
V+ = +5V  
50  
200  
500  
1000  
100  
V/V  
V/V  
V/V  
V/V  
V/V  
INA283  
INA284  
INA285  
INA286  
Gain Error  
INA282, INA283, INA286  
INA284, INA285  
vs Temperature  
OUTPUT  
±0.4  
±0.4  
±1.4  
±1.5  
%
%
0.0008  
0.005  
%/°C  
Nonlinearity Error  
Output Impedance  
Maximum Capacitive Load  
±0.01  
1.5  
1
%
Ω
No sustained oscillation  
nF  
(1) RTI = referred-to-input.  
(2) See typical characteristic graph Figure 20 .  
(3) The average of the voltage on pins REF1 and REF2 must be between VGND and the lesser of (VGND+9V) and V+.  
(4) Reference divider accuracy specifies the match between the reference divider resistors using the configuration in Figure 37.  
(5) See typical characteristic graph Figure 25.  
Copyright © 2009–2010, Texas Instruments Incorporated  
Submit Documentation Feedback  
3
Product Folder Link(s): INA282 INA283 INA284 INA285 INA286  
 
INA282, INA283  
INA284, INA285  
INA286  
SBOS485A –NOVEMBER 2009–REVISED JULY 2010  
www.ti.com  
ELECTRICAL CHARACTERISTICS (continued)  
Boldface limits apply over the specified temperature range, TA = –40°C to +125°C.  
At TA = +25°C, V+ = 5V, V+IN = 12V, VREF1 = VREF2 = 2.048V referenced to GND, and VSENSE = V+IN – V–IN, unless otherwise  
noted.  
INA282, INA283,  
INA284, INA285, INA286  
PARAMETER  
VOLTAGE OUTPUT(6)  
CONDITIONS  
RL = 10kΩ to GND  
V+ = 5V  
MIN  
TYP  
MAX  
UNIT  
Swing to V+ Power-Supply Rail  
Swing to GND  
(V+)–0.17  
(V+)–0.4  
V
V
GND+0.015  
GND+0.04  
FREQUENCY RESPONSE  
Effective Bandwidth(7)  
INA282  
BW  
10  
10  
4
kHz  
kHz  
kHz  
kHz  
kHz  
INA283  
INA284  
INA285  
2
INA286  
10  
NOISE, RTI(8)  
Voltage Noise Density  
POWER SUPPLY  
Specified Voltage Range  
Quiescent Current  
TEMPERATURE RANGE  
Specified Range  
1kHz  
110  
600  
nV/√Hz  
VS  
+2.7  
+18  
V
IQ  
900  
mA  
–40  
+125  
°C  
(6) See typical characteristic graphs Figure 29 through Figure 31.  
(7) See typical characteristic graph Figure 15 and the Effective Bandwidth section in the Applications Information.  
(8) RTI = referred-to-input.  
4
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Copyright © 2009–2010, Texas Instruments Incorporated  
Product Folder Link(s): INA282 INA283 INA284 INA285 INA286  
INA282, INA283  
INA284, INA285  
INA286  
www.ti.com  
SBOS485A –NOVEMBER 2009–REVISED JULY 2010  
PIN CONFIGURATION  
D PACKAGE  
SOIC-8  
(TOP VIEW)  
-IN  
GND  
1
2
3
4
8
7
6
5
+IN  
REF1  
V+  
REF2  
NC(1)  
OUT  
(1) NC: This pin is not internally connected. The NC pin should either be left floating or connected to GND.  
PIN DESCRIPTIONS  
SOIC-8  
PIN NO.  
NAME  
–IN  
DESCRIPTION  
Connection to negative side of shunt resistor.  
1
2
3
4
5
6
7
8
GND  
REF2  
NC  
Ground  
Reference voltage connection - See application section for connection options.  
This pin is not internally connected. The NC pin should either be left floating or connected to GND.  
Output voltage  
OUT  
V+  
Power supply  
REF1  
+IN  
Reference voltage connection - See application section for connection options.  
Connection to positive side of shunt resistor.  
Copyright © 2009–2010, Texas Instruments Incorporated  
Submit Documentation Feedback  
5
Product Folder Link(s): INA282 INA283 INA284 INA285 INA286  
INA282, INA283  
INA284, INA285  
INA286  
SBOS485A –NOVEMBER 2009–REVISED JULY 2010  
www.ti.com  
TYPICAL CHARACTERISTICS  
At TA = +25°C, V+ = 5V, V+IN = 12V, VREF1 = VREF2 = 2.048V referenced to GND, and VSENSE = V+IN – V–IN, unless otherwise  
noted.  
START-UP TRANSIENT RESPONSE  
START-UP TRANSIENT RESPONSE  
VREF = GND, VDRIVE = 0.125V, RLOAD = 10kW, CLOAD = 10pF  
VOUT  
CLOAD = 10pF  
VREF = GND  
VOUT  
VDRIVE = 0.125V  
RLOAD = 10kW  
V+  
V+  
25ms/div  
250ms/div  
Figure 1.  
Figure 2.  
12V COMMON-MODE STEP RESPONSE  
12V COMMON-MODE STEP RESPONSE  
VOUT  
VOUT  
VCM  
VCM  
2.5ms/div  
2.5ms/div  
Figure 3.  
Figure 4.  
12V COMMON-MODE STEP RESPONSE  
12V COMMON-MODE STEP RESPONSE  
VOUT  
VOUT  
VCM  
VCM  
2.5ms/div  
2.5ms/div  
Figure 5.  
Figure 6.  
6
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Copyright © 2009–2010, Texas Instruments Incorporated  
Product Folder Link(s): INA282 INA283 INA284 INA285 INA286  
 
INA282, INA283  
INA284, INA285  
INA286  
www.ti.com  
SBOS485A –NOVEMBER 2009–REVISED JULY 2010  
TYPICAL CHARACTERISTICS (continued)  
At TA = +25°C, V+ = 5V, V+IN = 12V, VREF1 = VREF2 = 2.048V referenced to GND, and VSENSE = V+IN – V–IN, unless otherwise  
noted.  
50V COMMON-MODE STEP RESPONSE  
50V COMMON-MODE STEP RESPONSE  
VOUT  
VCM  
VOUT  
VCM  
5ms/div  
5ms/div  
Figure 7.  
Figure 8.  
100mV STEP RESPONSE  
500mV STEP RESPONSE  
10ms/div  
10ms/div  
Figure 9.  
Figure 10.  
4V STEP RESPONSE  
17V STEP RESPONSE  
25ms/div  
25ms/div  
Figure 11.  
Figure 12.  
Copyright © 2009–2010, Texas Instruments Incorporated  
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7
Product Folder Link(s): INA282 INA283 INA284 INA285 INA286  
 
INA282, INA283  
INA284, INA285  
INA286  
SBOS485A –NOVEMBER 2009–REVISED JULY 2010  
www.ti.com  
TYPICAL CHARACTERISTICS (continued)  
At TA = +25°C, V+ = 5V, V+IN = 12V, VREF1 = VREF2 = 2.048V referenced to GND, and VSENSE = V+IN – V–IN, unless otherwise  
noted.  
INA282 PSRR (RTI)  
INPUT OVERLOAD  
vs FREQUENCY  
120  
110  
100  
90  
Input Drive (1V to 0V)  
VOUT (5V to midsupply)  
80  
70  
60  
50  
40  
30  
20  
25ms/div  
100  
1k  
10k  
100k  
1M  
100k  
1M  
Frequency (Hz)  
Figure 13.  
Figure 14.  
INA284  
GAIN vs FREQUENCY  
COMMON-MODE REJECTION RATIO (RTI)  
60  
50  
150  
140  
130  
120  
110  
100  
90  
40  
30  
20  
10  
INA282 (50V/V)  
INA285 (1kV/V)  
INA284 (500V/V)  
INA283 (200V/V)  
INA286 (100V/V)  
0
-10  
-20  
80  
70  
10  
100  
1k  
10k  
100k  
1M  
1
10  
100  
1k  
10k  
Frequency (Hz)  
Frequency (Hz)  
Figure 15.  
Figure 16.  
INA282 COMMON-MODE  
SLEW RATE INDUCED OFFSET  
INA286 OUTPUT IMPEDANCE  
vs FREQUENCY  
0.1  
1k  
100  
10  
0.01  
0.001  
0.0001  
1
0.00001  
0.000001  
0.1  
10  
100  
1k  
10k  
100k  
1k  
10k  
100k  
1M  
Frequency (Hz)  
VCM Slew Rate (V/sec)  
Figure 17.  
Figure 18.  
8
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Copyright © 2009–2010, Texas Instruments Incorporated  
Product Folder Link(s): INA282 INA283 INA284 INA285 INA286  
 
 
INA282, INA283  
INA284, INA285  
INA286  
www.ti.com  
SBOS485A –NOVEMBER 2009–REVISED JULY 2010  
TYPICAL CHARACTERISTICS (continued)  
At TA = +25°C, V+ = 5V, V+IN = 12V, VREF1 = VREF2 = 2.048V referenced to GND, and VSENSE = V+IN – V–IN, unless otherwise  
noted.  
INA282 TYPICAL NONLINEARITY  
vs OUTPUT VOLTAGE  
INA283 +IN BIAS CURRENT  
vs COMMON-MODE VOLTAGE  
0.06  
0.04  
0.02  
0
30  
20  
VSENSE = -50mV to +50mV  
V+ = 5V  
V+ = 2.7V  
V+ = 18V  
10  
0
V+ = 18V  
-10  
-20  
-30  
-40  
-0.02  
-0.04  
-0.06  
V+ = 3.5V  
-20 -10  
0
10  
20  
30  
40  
50  
60  
70  
80  
0
3
6
9
12  
15  
18  
Common-Mode Voltage (V)  
VOUT (V)  
Figure 19.  
Figure 20.  
INA283 QUIESCENT CURRENT  
vs COMMON-MODE VOLTAGE  
QUIESCENT CURRENT  
vs SUPPLY VOLTAGE  
900  
850  
800  
750  
700  
650  
600  
550  
500  
450  
400  
900  
800  
700  
600  
500  
400  
300  
200  
100  
0
V+ = 18V  
V+ = 5V  
V+ = 2.7V  
-20  
0
20  
40  
60  
80  
2
4
6
8
10  
12  
14  
16  
18  
Common-Mode Voltage (V)  
Supply Voltage (V)  
Figure 21.  
Figure 22.  
COMMON-MODE REJECTION RATIO  
vs TEMPERATURE  
QUIESCENT CURRENT  
vs TEMPERATURE  
170  
160  
150  
140  
130  
120  
110  
100  
90  
980  
880  
780  
680  
580  
480  
380  
280  
180  
80  
V+ = 18V  
V+ = 12V  
V+ = 5V  
V+ = 5V  
V+ = 2.7V  
80  
-75 -50 -25  
0
25  
50  
75  
100 125 150  
-75 -50 -25  
0
25  
50  
75  
100 125 150  
Temperature (°C)  
Temperature (°C)  
Figure 23.  
Figure 24.  
Copyright © 2009–2010, Texas Instruments Incorporated  
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Product Folder Link(s): INA282 INA283 INA284 INA285 INA286  
INA282, INA283  
INA284, INA285  
INA286  
SBOS485A –NOVEMBER 2009–REVISED JULY 2010  
www.ti.com  
TYPICAL CHARACTERISTICS (continued)  
At TA = +25°C, V+ = 5V, V+IN = 12V, VREF1 = VREF2 = 2.048V referenced to GND, and VSENSE = V+IN – V–IN, unless otherwise  
noted.  
+IN BIAS CURRENT  
GAIN vs TEMPERATURE  
vs TEMPERATURE  
1.0  
0.8  
0
-5  
0.6  
-10  
-15  
-20  
-25  
-30  
-35  
-40  
0.4  
V+ = 2.7V  
V+ = 5V  
0.2  
0
V+ = 5V  
-0.2  
-0.4  
-0.6  
-0.8  
-1.0  
V+ = 12V  
V+ = 18V  
VCM = 0V  
-75 -50 -25  
0
25  
50  
75  
100 125 150  
-75 -50 -25  
0
25  
50  
75  
100 125 150  
Temperature (°C)  
Temperature (°C)  
Figure 25.  
Figure 26.  
INA282 0.1Hz TO 10Hz VOLTAGE NOISE, RTI  
INA282 VOLTAGE NOISE vs FREQUENCY  
6.0  
0.12  
0.11  
0.10  
0.09  
0.08  
0.07  
0.06  
5.5  
5.0  
4.5  
4.0  
3.5  
3.0  
100  
1k  
10k  
100k  
Time (1s/div)  
Frequency (Hz)  
Figure 27.  
Figure 28.  
INA284 SWING TO RAIL WITH SHORT-CIRCUIT CURRENT  
INA283 SWING TO RAIL vs OUTPUT CURRENT  
18  
16  
14  
12  
10  
8
0
800  
700  
600  
500  
400  
300  
200  
100  
0
Source 5V  
ISC = 5.2mA  
-2  
+25°C  
Source 2.7V  
ISC = 3.4mA  
+85°C  
-4  
+125°C  
-6  
Source 18V  
ISC = 5.8mA  
Sink 18V  
ISC = 8.6mA  
-8  
-10  
-12  
-14  
-16  
-18  
-40°C  
6
Sink 2.7V  
ISC = 6.2mA  
4
2.7V Swing  
5V Swing  
Sink 5V  
ISC = 8.2mA  
2
0
0
1
2
3
4
5
6
7
8
9
10  
0
0.2 0.4 0.6 0.8 1.0 1.2 1.4 1.6 1.8 2.0  
IOUT, Sourcing (mA)  
IOUT (mA)  
Figure 29.  
Figure 30.  
10  
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TYPICAL CHARACTERISTICS (continued)  
At TA = +25°C, V+ = 5V, V+IN = 12V, VREF1 = VREF2 = 2.048V referenced to GND, and VSENSE = V+IN – V–IN, unless otherwise  
noted.  
INA283 SWING TO GROUND vs OUTPUT CURRENT  
400  
350  
300  
250  
+125°C  
200  
150  
100  
2.7V Swing  
5V Swing  
+85°C  
50  
18V Swing  
2.0  
+25°C  
-40°C  
1.0  
0
0
0.5  
1.5  
2.5  
IOUT, Sinking (mA)  
Figure 31.  
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APPLICATIONS INFORMATION  
GENERAL INFORMATION  
The INA282 family voltage output current shunt monitors feature a common-mode range that extends 14V below  
the negative supply rail, as well as up to 80V, which allows use for either low-side or high-side current sensing.  
BASIC CONNECTIONS  
Figure 32 shows the basic connection of an INA282 family device. The input pins, +IN and –IN, should be  
connected as closely as possible to the shunt resistor to minimize any resistance in series with the shunt  
resistance.  
Supply  
-14V to +80V  
+2.7V to +18V  
Load  
+IN  
-IN  
V+  
1
Æ2  
Æ2  
Æ1  
Æ2  
Æ2  
1
Æ1  
OUT  
ZerÆ-  
Drift  
Output  
GAIN  
PRODUCT  
50V/V  
INA282  
INA286  
INA283  
INA284  
INA285  
100V/V  
200V/V  
500V/V  
1000V/V  
33.3kW  
33.3kW  
REF2  
REF1  
GND  
Figure 32. Typical Application  
Power-supply bypass capacitors are required for stability. Applications with noisy or high-impedance power  
supplies may require additional decoupling capacitors to reject power-supply noise. Connect bypass capacitors  
close to the device pins.  
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POWER SUPPLY  
The INA282 family can make accurate measurements well outside of its own power-supply voltage, V+, because  
its inputs (+IN and –IN) may operate anywhere between –14V and +80V independent of V+. For example, the V+  
power supply can be 5V while the common-mode voltage being monitored by the shunt may be as high as +80V.  
Of course, the output voltage range of the INA282 family is constrained by the supply voltage that powers it on  
V+. Note that when the power to the INA282 family is off (that is, no voltage is supplied to the V+ pin), the input  
pins (+IN and –IN) are high impedance with respect to ground and typically leak less than ±1mA over the full  
common-mode range of –14V to +80V  
SELECTING RS  
The Zerø-Drift architecture of the INA282 family enables use with full-scale range shunt voltages as low as  
10mV.  
EFFECTIVE BANDWIDTH  
The extremely high dc CMRR of the INA282 family results from the switched capacitor input structure. Because  
of this architecture, the INA28x exhibits discrete time system behaviors as illustrated in the gain versus frequency  
graph of Figure 16 and the step response curves of Figure 3 through Figure 10. The response to a step input  
depends somewhat on the phase of the internal INA28x clock when the input step occurs. It is possible to  
overload the input amplifier with a rapid change in input common-mode voltage (see Figure 17). Errors as a  
result of common-mode voltage steps and/or overload situations typically disappear within 15ms after the  
disturbance is removed.  
TRANSIENT PROTECTION  
The –14V to +80V common-mode range of the INA282 family is ideal for withstanding automotive fault conditions  
that range from 12V battery reversal up to +80V transients; no additional protective components are needed up  
to those levels. In the event that the INA282 family is exposed to transients on the inputs in excess of its ratings,  
then external transient absorption with semiconductor transient absorbers (Zener or Transzorbs) will be  
necessary. Use of MOVs or VDRs is not recommended except when they are used in addition to a  
semiconductor transient absorber. Select the transient absorber such that it cannot allow the INA282 family to be  
exposed to transients greater than 80V (that is, allow for transient absorber tolerance, as well as additional  
voltage as a result of transient absorber dynamic impedance). Despite the use of internal zener-type electrostatic  
discharge (ESD) protection, the INA282 family does not lend itself to using external resistors in series with the  
inputs without degrading gain accuracy.  
SHUTDOWN  
While the INA282 family does not provide a shutdown pin, the quiescent current of 600mA enables it to be  
powered from the output of a logic gate. Take the gate low to shut down the INA282 family devices.  
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REFERENCE PIN CONNECTION OPTIONS  
Figure 33 illustrates a test circuit for reference divider accuracy. The output of the INA282 family can be  
connected for unidirectional or bidirectional operation. Note that neither the REF1 pin nor the REF2 pin may be  
connected to any voltage source lower than GND or higher than V+, and that the effective reference voltage  
(REF1 + REF2)/2 must be 9V or less. This parameter means that the V+ reference output connection shown in  
Figure 35 is not allowed for V+ greater than 9V. However, the split-supply reference connection shown in  
Figure 37 is allowed for all values of V+ up to 18V.  
V+  
+IN  
-IN  
V+  
Æ1  
Æ2  
Æ2  
Æ1  
Æ2  
Æ2  
See Note (1)  
Æ1  
Æ1  
OUT  
ZerÆ-  
Drift  
GAIN  
PRODUCT  
50V/V  
INA282  
INA286  
INA283  
INA284  
INA285  
100V/V  
200V/V  
500V/V  
1000V/V  
33.3kW  
33.3kW  
REF2  
REF1  
GND  
(1) Reference divider accuracy is determined by measuring the output with the reference voltage applied to alternate reference resistors, and  
calculating a result such that the amplifier offset is cancelled in the final measurement.  
Figure 33. Test Circuit for Reference Divider Accuracy  
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UNIDIRECTIONAL OPERATION  
Unidirectional operation allows the INA282 family to measure currents through a resistive shunt in one direction.  
In the case of unidirectional operation, the output could be set at the negative rail (near ground, and the most  
common connection) or at the positive rail (near V+) when the differential input is 0V. The output moves to the  
opposite rail when a correct polarity differential input voltage is applied.  
The required polarity of the differential input depends on the output voltage setting. If the output is set at the  
positive rail, the input polarity must be negative to move the output down. If the output is set at ground, the  
polarity is positive to move the output up.  
The following sections describe how to configure the output for unidirectional operation.  
Ground Referenced Output  
When using the INA282 family in this mode, both reference inputs are connected to ground; this configuration  
takes the output to the negative rail when there is 0V differential at the input (as Figure 34 shows).  
Supply  
-14V to +80V  
Load  
V+  
+IN  
-IN  
V+  
Æ1  
Æ2  
Æ2  
Æ1  
Æ2  
Æ2  
Æ1  
Æ1  
OUT  
ZerÆ-  
Drift  
Output  
GAIN  
PRODUCT  
50V/V  
INA282  
INA286  
INA283  
INA284  
INA285  
33.3kW  
33.3kW  
100V/V  
200V/V  
500V/V  
1000V/V  
REF2  
REF1  
GND  
Figure 34. Ground Referenced Output  
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V+ Referenced Output  
This mode is set when both reference pins are connected to the positive supply. It is typically used when a  
diagnostic scheme requires detection of the amplifier and the wiring before power is applied to the load (as  
shown in Figure 35).  
ISENSE  
Supply  
-14V to +80V  
Load  
V+  
V+  
+IN  
-IN  
Æ1  
Æ2  
Æ2  
Æ1  
Æ2  
Æ2  
Æ1  
Æ1  
OUT  
ZerÆ-  
Drift  
Output  
GAIN  
PRODUCT  
50V/V  
INA282  
INA286  
INA283  
INA284  
INA285  
33.3kW  
33.3kW  
100V/V  
200V/V  
500V/V  
1000V/V  
REF2  
REF1  
GND  
Figure 35. V+ Referenced Output  
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BIDIRECTIONAL OPERATION  
Bidirectional operation allows the INA282 family to measure currents through a resistive shunt in two directions.  
In this case, the output can be set anywhere within the limits of what the reference inputs allow (that is, between  
0V to 9V, but never to exceed the supply voltage). Typically, it is set at half-scale for equal range in both  
directions. In some cases, however, it is set at a voltage other than half-scale when the bidirectional current is  
nonsymmetrical.  
The quiescent output voltage is set by applying voltage(s) to the reference inputs. REF1 and REF2 are  
connected to internal resistors that connect to an internal offset node. There is no operational difference between  
the pins.  
External Reference Output  
Connecting both pins together and to a reference produces an output at the reference voltage when there is no  
differential input; this configuration is illustrated in Figure 36. The output moves down from the reference voltage  
when the input is negative relative to the –IN pin and up when the input is positive relative to the –IN pin. Note  
that this technique is the most accurate way to bias the output to a precise voltage.  
Supply  
-14V to +80V  
Load  
V+  
V+  
+IN  
-IN  
Æ1  
Æ2  
Æ2  
Æ1  
Æ2  
Æ2  
Æ1  
Æ1  
OUT  
ZerÆ-  
Drift  
Output  
GAIN  
PRODUCT  
50V/V  
INA282  
INA286  
INA283  
INA284  
INA285  
33.3kW  
33.3kW  
REF3020  
100V/V  
200V/V  
500V/V  
1000V/V  
REF2  
REF1  
2.048V  
Reference  
GND  
Figure 36. External Reference Output  
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Splitting the Supply  
By connecting one reference pin to V+ and the other to the ground pin, the output is set at half of the supply  
when there is no differential input, as shown in Figure 37. This method creates a midscale offset that is  
ratiometric to the supply voltage; thus, if the supply increases or decreases, the output remains at half the  
supply.  
Supply  
-14V to +80V  
Load  
V+  
+IN  
-IN  
V+  
Æ1  
Æ2  
Æ2  
Æ1  
Æ2  
Æ2  
Æ1  
Æ1  
OUT  
ZerÆ-  
Drift  
Output  
GAIN  
PRODUCT  
50V/V  
INA282  
INA286  
INA283  
INA284  
INA285  
33.3kW  
33.3kW  
100V/V  
200V/V  
500V/V  
1000V/V  
REF2  
REF1  
GND  
Figure 37. Split-Supply Output  
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Splitting an External Reference  
In this case, an external reference is divided by 2 with an accuracy of approximately 0.5% by connecting one  
REF pin to ground and the other REF pin to the reference (as Figure 38 illustrates).  
Supply  
-14V to +80V  
Load  
V+  
+IN  
-IN  
V+  
Æ1  
Æ2  
Æ2  
Æ1  
Æ2  
Æ2  
Æ1  
Æ1  
OUT  
ZerÆ-  
Drift  
Output  
GAIN  
PRODUCT  
50V/V  
INA282  
INA286  
INA283  
INA284  
INA285  
33.3kW  
33.3kW  
REF02  
100V/V  
200V/V  
500V/V  
1000V/V  
REF2  
REF1  
5V  
Reference  
GND  
Figure 38. Split Reference Output  
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EXTENDED NEGATIVE COMMON-MODE RANGE  
Using a negative power supply can extend the common-mode range 14V more negative than the supply used.  
For instance, a –10V supply allows up to –24V negative common-mode. Remember to keep the total voltage  
between the GND pin and V+ pin to less than 18V. The positive common-mode decreases by the same amount.  
The reference input simplifies this type of operation because the output quiescent bias point is always based on  
the reference connections. Figure 39 shows a circuit configuration for common-mode ranges from –24V to +70V.  
Supply  
-24V to +70V  
Load  
V+ = 5V  
+IN  
-IN  
V+  
1
Æ2  
Æ2  
Æ1  
Æ2  
Æ2  
Æ1  
Æ1  
OUT  
ZerÆ-  
Drift  
PRODUCT  
GAIN  
INA282  
INA283  
INA284  
INA285  
INA286  
50V/V  
200V/V  
500V/V  
1000V/V  
100V/V  
33.3kW  
33.3kW  
REF2  
REF1  
See Note (1)  
GND  
Connect to -10V  
(1) Connect the REF pins as desired; however, they cannot exceed 9V above the GND pin voltage.  
Figure 39. Circuit Configuration for Common-Mode Ranges from –24V to +70V  
CALCULATING TOTAL ERROR  
The electrical specifications for the INA282-286 family of devices include the typical individual errors terms such  
as gain error, offset error, and nonlinearity error. Total error including all of these individual error components is  
not specified in the Electrical Characteristics table. In order to accurately calculate the error that can be expected  
from the device, we must first know the operating conditions to which the device is subjected. Some current  
shunt monitors specify a total error in the product data sheet. However, this total error term is accurate under  
only one particular set of operating conditions. Specifying the total error at this one point has little practical value  
because any deviation from these specific operating conditions no longer yields the same total error value. This  
section discusses the individual error sources, with information on how to apply them in order to calculate the  
total error value for the device under any normal operating conditions.  
The typical error sources that have the largest impact on the total error of the device are input offset voltage,  
common-mode voltage rejection, gain error and nonlinearity error. For the INA282-286, an additional error source  
referred to as Reference Common-Mode Rejection is also included in the total error value.  
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The nonlinearity error of the INA282-286 is relatively low compared to the gain error specification, which results  
in a gain error that can be expected to be relatively constant throughout the linear input range of the device.  
While the gain error remains constant across the linear input range of the device, the error associated with the  
input offset voltage does not. As the differential input voltage developed across a shunt resistor at the input of the  
INA282-286 decreases, the inherent input offset voltage of the device becomes a larger percentage of the  
measured input signal resulting in an increase in error in the measurement. This varying error is present among  
all current shunt monitors, given the input offset voltage ratio to the voltage being sensed by the device. The  
relatively low input offset voltages present in the INA282-286 devices limit the amount of contribution the offset  
voltage has on the total error term.  
The term Reference Common-Mode Rejection refers to the amount of error induced by applying a reference  
voltage to the INA282-286 device that deviates from the inherent bias voltage present at the output of the first  
stage of the device. The output of the switched-capacitor network and first-stage amplifier has an inherent bias  
voltage of approximately 2.048V. Applying a reference voltage of 2.048V to the INA282-286 reference pins  
results in no additional error term contribution. Applying a voltage to the reference pins that differs from 2.048V  
creates a voltage potential in the internal difference amplifier, resulting in additional current flowing through the  
resistor network. As a result of resistor tolerances, this additional current flow causes additional error at the  
output because of resistor mismatches. Additionally, as a result of resistor tolerances, this additional current flow  
causes additional error at the output based on the common-mode rejection ratio of the output stage amplifier.  
This error term is referred back to the input of the device as additional input offset voltage. Increasing the  
difference between the 2.048V internal bias and the external reference voltage results in a higher input offset  
voltage. Also, as the error at the output is referred back to the input, there is a larger impact on the input-referred  
offset, VOS, for the lower-gain versions of the device.  
Two examples are provided that detail how different operating conditions can affect the total error calculations.  
Typical and maximum calculations are shown as well to provide the user more information on how much error  
variance could be present from device to device.  
Example 1  
INA282; VS = 5V; VCM = 12V; VREF = 2.048V; VSENSE = 10mV  
Table 1. Example 1  
TERM  
SYMBOL  
EQUATION  
TYPICAL VALUE  
MAXIMUM VALUE  
Initial Input Offset  
Voltage  
VOS  
—
20mV  
70mV  
Added Input Offset  
Voltage Because of  
Common-Mode  
Voltage  
1
CMRR_dB  
´ (VCM - 12V)  
(
VOS_CM  
0mV  
0mV  
(
20  
10  
Added Input Offset  
Voltage Because of  
Reference Voltage  
R
CMR ´ (2.048V - VREF)  
VOS_REF  
VOS_Total  
Error_VOS  
0mV  
20mV  
0.20%  
0mV  
70mV  
0.70%  
Total Input Offset  
Voltage  
2
(VOS)2 + (VOS_CM)2 + (VOS_REF  
)
VOS_Total  
Error from Input  
Offset Voltage  
´ 100  
VSENSE  
Gain Error  
Error_Gain  
Error_Lin  
—
—
0.40%  
0.01%  
1.40%  
0.01%  
Nonlinearity Error  
(Error_VOS)2 + (Error_Gain)2 + (Error_Lin)2  
Total Error  
—
0.45%  
1.56%  
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Example 2  
INA286; VS = 5V; VCM = 24V; VREF = 0V; VSENSE = 10mV  
Table 2. Example 2  
TERM  
SYMBOL  
EQUATION  
TYPICAL VALUE  
MAXIMUM VALUE  
Initial Input Offset  
Voltage  
VOS  
—
20mV  
70mV  
Added Input Offset  
Voltage Because of  
Common-Mode  
Voltage  
1
CMRR_dB  
´ (VCM - 12V)  
(
VOS_CM  
1.2mV  
12mV  
(
20  
10  
Added Input Offset  
Voltage Because of  
Reference Voltage  
R
CMR ´ (2.048V - VREF)  
VOS_REF  
VOS_Total  
Error_VOS  
34.8mV  
40.2mV  
0.40%  
92.2mV  
116.4mV  
1.16%  
Total Input Offset  
Voltage  
2
(VOS)2 + (VOS_CM)2 + (VOS_REF  
)
VOS_Total  
Error from Input  
Offset Voltage  
´ 100  
VSENSE  
Gain Error  
Error_Gain  
Error_Lin  
—
—
0.40%  
0.01%  
1.40%  
0.01%  
Nonlinearity Error  
(Error_VOS)2 + (Error_Gain)2 + (Error_Lin)2  
Total Error  
—
0.57%  
1.82%  
SUMMING CURRENTS AND PARALLELING  
The outputs of multiple INA282 family devices are easily summed by connecting the output of one INA282 family  
device to the reference input of a second INA282 family device. Summing beyond two devices is possible by  
repeating this connection, and is shown for three devices in Figure 40. The reference input of the first INA282  
family device sets the output quiescent level for all the devices in the string.  
First Circuit  
Second Circuit  
Third Circuit  
VIN+  
VIN-  
VIN+  
VIN-  
VIN+  
VIN-  
Æ1  
Æ2  
Æ2  
Æ1  
Æ1  
Æ2  
Æ2  
Æ1  
Æ1  
Æ2  
Æ2  
Æ1  
Æ2  
Æ2  
Æ2  
Æ2  
Æ2  
Æ2  
Æ1  
Æ1  
Æ1  
Æ1  
Output  
Output  
Output  
Summed  
Output  
VREF  
GND  
GND  
GND  
V+  
V+  
V+  
NOTE: The voltage applied to the reference inputs cannot exceed 9V.  
Figure 40. Summing the Outputs of Multiple INA282 Family Devices  
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CURRENT DIFFERENCING  
Occasionally, the need arises to confirm that the current into a load is identical to the current out of a load,  
usually as part of diagnostic testing or fault detection. This situation requires precision current differencing, which  
is the same as summing except that the two amplifiers have the inputs connected opposite of each other. Under  
normal operating conditions, the final output is very close to the reference value and proportional to any current  
difference. Figure 41 is an example of the connections required for current differencing.  
First Circuit  
Second Circuit  
Supply  
Load  
VIN+  
VIN-  
VIN+  
VIN-  
Æ1  
Æ2  
Æ2  
Æ1  
Æ1  
Æ2  
Æ2  
Æ1  
Æ2  
Æ2  
Æ2  
Æ2  
Æ1  
Æ1  
Æ1  
Æ1  
Output  
Output  
Difference  
Output  
VREF  
GND  
GND  
V+  
V+  
NOTE: This example is identical to the current summing example, except that the two shunt inputs are reversed in polarity,  
this current differencing circuit is useful in detecting when current into and out of a load do not match.  
Figure 41. Current Differencing Using an INA282 Family Device  
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COMMON-MODE DYNAMICS AND CURRENT DIFFERENCING  
Current sensing is frequently used on totem-pole output stages, such as those of bridge-type motor drives. We  
can sense current in one of three locations on a totem-pole output: on the ground side (low-side sensing); on the  
power-supply side (high-side sensing); or on the output (phase sensing). Only the output line reports the exact  
load current. Obviously, the ground and supply-side sensing report only the current in the individual respective  
phases. Figure 42 depicts these various methods on a three-phase motor driver.  
Motor  
High Side  
Current  
Sense  
High Side  
Current  
Sense  
High Side  
Current  
Sense  
Phase  
Current  
Sense  
Phase  
Current  
Sense  
Phase  
Current  
Sense  
Low Side  
Current Sense  
Low Side  
Current Sense  
Low Side  
Current Sense  
NOTE: Motor drive current sensing can be done on the low side, phase side, or high side. Only the phase output gives  
complete information regarding current in the motor, but is subject to common-mode transients that even the best  
amplifiers do not reject completely.  
Figure 42. Motor Drive Current Sensing  
However, sensing on the output is subject to large common-mode voltage steps that result in feedthrough in  
even the best amplifiers. The ground and supply-side sensing configurations are free of this problem, thanks to  
the static common-mode environments. Sensing either ground or supply alone only provides partial information  
regarding motor current, but sense them individually and sum them and we have the same information provided  
by phase sensing, with an added advantage of not being subject to transient common-mode artifacts. See  
Figure 43 for an illustration of two INA282 family devices connected in this manner. Technically, this  
configuration is current differencing, though, because we want the upper sense to report a positive-going  
excursion in the overall output, and the negative sense to report a negative-going excursion.  
24  
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Copyright © 2009–2010, Texas Instruments Incorporated  
Product Folder Link(s): INA282 INA283 INA284 INA285 INA286  
 
INA282, INA283  
INA284, INA285  
INA286  
www.ti.com  
SBOS485A –NOVEMBER 2009–REVISED JULY 2010  
Motor  
Supply  
(< 80V)  
+2.7V to  
+18V  
VIN-  
VIN+  
Q1  
D1  
D2  
MOSFET  
Drive  
Circuits  
VREF  
Output  
Q2  
+2.7V to  
+18V  
VIN-  
VIN+  
NOTE: By sensing totem-pole current on both the positive and negative rail and summing, dynamic common-mode issues  
can be avoided entirely. Note that IC2 is connected with inverting inputs because it should report current with an  
opposite polarity to that of IC1.  
Figure 43. Sensing and Summing Totem Pole Current  
Copyright © 2009–2010, Texas Instruments Incorporated  
Submit Documentation Feedback  
25  
Product Folder Link(s): INA282 INA283 INA284 INA285 INA286  
PACKAGE OPTION ADDENDUM  
www.ti.com  
5-Mar-2011  
PACKAGING INFORMATION  
Status (1)  
Eco Plan (2)  
MSL Peak Temp (3)  
Samples  
Orderable Device  
Package Type Package  
Drawing  
Pins  
Package Qty  
Lead/  
Ball Finish  
(Requires Login)  
INA282AID  
ACTIVE  
ACTIVE  
SOIC  
SOIC  
D
D
8
8
75  
Green (RoHS  
& no Sb/Br)  
CU NIPDAU Level-2-260C-1 YEAR  
INA282AIDR  
2500  
Green (RoHS  
& no Sb/Br)  
CU NIPDAU Level-2-260C-1 YEAR  
(1) The marketing status values are defined as follows:  
ACTIVE: Product device recommended for new designs.  
LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect.  
NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in a new design.  
PREVIEW: Device has been announced but is not in production. Samples may or may not be available.  
OBSOLETE: TI has discontinued the production of the device.  
(2) Eco Plan - The planned eco-friendly classification: Pb-Free (RoHS), Pb-Free (RoHS Exempt), or Green (RoHS & no Sb/Br) - please check http://www.ti.com/productcontent for the latest availability  
information and additional product content details.  
TBD: The Pb-Free/Green conversion plan has not been defined.  
Pb-Free (RoHS): TI's terms "Lead-Free" or "Pb-Free" mean semiconductor products that are compatible with the current RoHS requirements for all 6 substances, including the requirement that  
lead not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered at high temperatures, TI Pb-Free products are suitable for use in specified lead-free processes.  
Pb-Free (RoHS Exempt): This component has a RoHS exemption for either 1) lead-based flip-chip solder bumps used between the die and package, or 2) lead-based die adhesive used between  
the die and leadframe. The component is otherwise considered Pb-Free (RoHS compatible) as defined above.  
Green (RoHS & no Sb/Br): TI defines "Green" to mean Pb-Free (RoHS compatible), and free of Bromine (Br) and Antimony (Sb) based flame retardants (Br or Sb do not exceed 0.1% by weight  
in homogeneous material)  
(3) MSL, Peak Temp. -- The Moisture Sensitivity Level rating according to the JEDEC industry standard classifications, and peak solder temperature.  
Important Information and Disclaimer:The information provided on this page represents TI's knowledge and belief as of the date that it is provided. TI bases its knowledge and belief on information  
provided by third parties, and makes no representation or warranty as to the accuracy of such information. Efforts are underway to better integrate information from third parties. TI has taken and  
continues to take reasonable steps to provide representative and accurate information but may not have conducted destructive testing or chemical analysis on incoming materials and chemicals.  
TI and TI suppliers consider certain information to be proprietary, and thus CAS numbers and other limited information may not be available for release.  
In no event shall TI's liability arising out of such information exceed the total purchase price of the TI part(s) at issue in this document sold by TI to Customer on an annual basis.  
Addendum-Page 1  
PACKAGE MATERIALS INFORMATION  
www.ti.com  
3-Aug-2010  
TAPE AND REEL INFORMATION  
*All dimensions are nominal  
Device  
Package Package Pins  
Type Drawing  
SPQ  
Reel  
Reel  
A0  
B0  
K0  
P1  
W
Pin1  
Diameter Width (mm) (mm) (mm) (mm) (mm) Quadrant  
(mm) W1 (mm)  
INA282AIDR  
SOIC  
D
8
2500  
330.0  
12.4  
6.4  
5.2  
2.1  
8.0  
12.0  
Q1  
Pack Materials-Page 1  
PACKAGE MATERIALS INFORMATION  
www.ti.com  
3-Aug-2010  
*All dimensions are nominal  
Device  
Package Type Package Drawing Pins  
SOIC  
SPQ  
Length (mm) Width (mm) Height (mm)  
346.0 346.0 29.0  
INA282AIDR  
D
8
2500  
Pack Materials-Page 2  
IMPORTANT NOTICE  
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