LM2587T-ADJ [TI]
LM2587 SIMPLE SWITCHER 5A Flyback Regulator; LM2587 SIMPLE SWITCHER 5A反激式稳压器
| 型号： | LM2587T-ADJ |
| 厂家： | 
TEXAS INSTRUMENTS |
| 描述： | LM2587 SIMPLE SWITCHER 5A Flyback Regulator |
| 文件： | 总32页 (文件大小：4160K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
LM2587
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SNVS115D –APRIL 2000–REVISED APRIL 2013
®
LM2587 SIMPLE SWITCHER 5A Flyback Regulator
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1
FEATURES
DESCRIPTION
The LM2587 series of regulators are monolithic
23
•
Requires Few External Components
integrated circuits specifically designed for flyback,
step-up (boost), and forward converter applications.
The device is available in 4 different output voltage
versions: 3.3V, 5.0V, 12V, and adjustable.
•
Family of Standard Inductors and
Transformers
•
•
•
NPN Output Switches 5.0A, can Stand Off 65V
Wide Input Voltage Range: 4V to 40V
Requiring
a
minimum number of external
components, these regulators are cost effective, and
simple to use. Included in the datasheet are typical
circuits of boost and flyback regulators. Also listed
are selector guides for diodes and capacitors and a
family of standard inductors and flyback transformers
designed to work with these switching regulators.
Current-Mode Operation for Improved
Transient Response, Line Regulation, and
Current Limit
•
•
100 kHz Switching Frequency
Internal Soft-Start Function Reduces In-Rush
Current During Start-Up
The power switch is a 5.0A NPN device that can
stand-off 65V. Protecting the power switch are current
and thermal limiting circuits, and an undervoltage
lockout circuit. This IC contains a 100 kHz fixed-
frequency internal oscillator that permits the use of
small magnetics. Other features include soft start
mode to reduce in-rush current during start up,
current mode control for improved rejection of input
voltage and output load transients and cycle-by-cycle
current limiting. An output voltage tolerance of ±4%,
within specified input voltages and output load
conditions, is ensured for the power supply system.
•
•
Output Transistor Protected by Current Limit,
Under Voltage Lockout, and Thermal
Shutdown
System Output Voltage Tolerance of ±4% Max
Over Line and Load Conditions
TYPICAL APPLICATIONS
•
•
•
•
Flyback Regulator
Multiple-Output Regulator
Simple Boost Regulator
Forward Converter
Flyback Regulator
Figure 1.
1
Please be aware that an important notice concerning availability, standard warranty, and use in critical applications of
Texas Instruments semiconductor products and disclaimers thereto appears at the end of this data sheet.
SIMPLE SWITCHER, Switchers Made Simple are registered trademarks of Texas Instruments.
All other trademarks are the property of their respective owners.
2
3
PRODUCTION DATA information is current as of publication date.
Products conform to specifications per the terms of the Texas
Instruments standard warranty. Production processing does not
necessarily include testing of all parameters.
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LM2587
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Connection Diagrams
Figure 2. Bent, Staggered Leads
Figure 3. Bent, Staggered Leads
5-Lead TO-220 (NDH)
Side View
5-Lead TO-220 (NDH)
Top View
Figure 4. 5-Lead TO-263 (KTT)
Top View
Figure 5. 5-Lead TO-263 (KTT)
Side View
For Fixed Versions 3.3V, R1 = 3.4k, R2 = 2k5V, R1 = 6.15k, R2 = 2k12V, R1 = 8.73k, R2 = 1kFor Adj. VersionR1 =
Short (0Ω), R2 = Open
Figure 6. Block Diagram
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Test Circuits
CIN1—100 μF, 25V Aluminum Electrolytic CIN2—0.1 μF CeramicT—22 μH, 1:1 Schott
#67141450D—1N5820COUT—680 μF, 16V Aluminum Electrolytic CC—0.47 μF Ceramic RC—2k
Figure 7. LM2587-3.3 and LM2587-5.0 Test Circuit
CIN1—100 μF, 25V Aluminum Electrolytic CIN2—0.1 μF CeramicL—15 μH, Renco #RL-5472-5D—1N5820COUT—680
μF, 16V Aluminum Electrolytic CC—0.47 μF Ceramic RC—2kFor 12V Devices: R1 = Short (0Ω) and R2 = Open For
ADJ Devices: R1 = 48.75k, ±0.1% and R2 = 5.62k, ±1%
Figure 8. LM2587-12 and LM2587-ADJ Test Circuit
Flyback Regulator Operation
The LM2587 is ideally suited for use in the flyback regulator topology. The flyback regulator can produce a single
output voltage, such as the one shown in Figure 9, or multiple output voltages. In Figure 9, the flyback regulator
generates an output voltage that is inside the range of the input voltage. This feature is unique to flyback
regulators and cannot be duplicated with buck or boost regulators.
The operation of a flyback regulator is as follows (refer to Figure 9): when the switch is on, current flows through
the primary winding of the transformer, T1, storing energy in the magnetic field of the transformer. Note that the
primary and secondary windings are out of phase, so no current flows through the secondary when current flows
through the primary. When the switch turns off, the magnetic field collapses, reversing the voltage polarity of the
primary and secondary windings. Now rectifier D1 is forward biased and current flows through it, releasing the
energy stored in the transformer. This produces voltage at the output.
The output voltage is controlled by modulating the peak switch current. This is done by feeding back a portion of
the output voltage to the error amp, which amplifies the difference between the feedback voltage and a 1.230V
reference. The error amp output voltage is compared to a ramp voltage proportional to the switch current (i.e.,
inductor current during the switch on time). The comparator terminates the switch on time when the two voltages
are equal, thereby controlling the peak switch current to maintain a constant output voltage.
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As shown in Figure 9, the LM2587 can be used as a flyback regulator by using a minimum number of external
components. The switching waveforms of this regulator are shown in Figure 22. Typical Performance Characteristics
observed during the operation of this circuit are shown in Figure 23.
Figure 9. 12V Flyback Regulator Design Example
These devices have limited built-in ESD protection. The leads should be shorted together or the device placed in conductive foam
during storage or handling to prevent electrostatic damage to the MOS gates.
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Absolute Maximum Ratings(1)(2)
Input Voltage
−0.4V ≤ VIN ≤ 45V
−0.4V ≤ VSW ≤ 65V
Internally Limited
−0.4V ≤ VCOMP ≤ 2.4V
−0.4V ≤ VFB ≤ 2 VOUT
−65°C to +150°C
260°C
Switch Voltage
Switch Current(3)
Compensation Pin Voltage
Feedback Pin Voltage
Storage Temperature Range
Lead Temperature
(Soldering, 10 sec.)
Temperature(4)
Maximum Junction
150°C
(4)
Power Dissipation
Internally Limited
2 kV
Minimum ESD Rating
(C = 100 pF, R = 1.5 kΩ)
(1) Absolute Maximum Ratings indicate limits beyond which damage to the device may occur. Operating ratings indicate conditions the
device is intended to be functional, but device parameter specifications may not be ensured under these conditions. For ensured
specifications and test conditions, see the Electrical Characteristics.
(2) If Military/Aerospace specified devices are required, please contact the TI Sales Office/ Distributors for availability and specifications.
(3) Note that switch current and output current are not identical in a step-up regulator. Output current cannot be internally limited when the
LM2587 is used as a step-up regulator. To prevent damage to the switch, the output current must be externally limited to 5A. However,
output current is internally limited when the LM2587 is used as a flyback regulator (see the Application Hints section for more
information).
(4) The junction temperature of the device (TJ) is a function of the ambient temperature (TA), the junction-to-ambient thermal resistance
(θJA), and the power dissipation of the device (PD). A thermal shutdown will occur if the temperature exceeds the maximum junction
temperature of the device: PD × θJA + TA(MAX) ≥ TJ(MAX). For a safe thermal design, check that the maximum power dissipated by the
device is less than: PD ≤ [TJ(MAX) − TA(MAX))]/θJA. When calculating the maximum allowable power dissipation, derate the maximum
junction temperature—this ensures a margin of safety in the thermal design.
Operating Ratings
Supply Voltage
4V ≤ VIN ≤ 40V
0V ≤ VSW ≤ 60V
Output Switch Voltage
Output Switch Current
Junction Temperature Range
ISW ≤ 5.0A
−40°C ≤ TJ ≤ +125°C
LM2587-3.3 Electrical Characteristics
Specifications with standard type face are for TJ = 25°C, and those in bold type face apply over full Operating Temperature
Range. Unless otherwise specified, VIN = 5V.
Symbol
Parameters
Conditions
Typical
Min
Max
Units
SYSTEM PARAMETERS Test Circuit of Figure 7(1)
VOUT
Output Voltage
Line Regulation
Load Regulation
Efficiency
VIN = 4V to 12V
ILOAD = 400 mA to 1.75A
3.3
20
20
75
3.17/3.14
3.43/3.46
50/100
V
ΔVOUT
ΔVIN
/
/
VIN = 4V to 12V
ILOAD = 400 mA
mV
mV
%
ΔVOUT
ΔILOAD
VIN = 12V
ILOAD = 400 mA to 1.75A
50/100
η
VIN = 12V, ILOAD = 1A
UNIQUE DEVICE PARAMETERS(2)
VREF
ΔVREF
GM
Output Reference
Voltage
Measured at Feedback Pin
VCOMP = 1.0V
3.3
2.0
3.242/3.234
3.358/3.366
V
Reference Voltage
Line Regulation
VIN = 4V to 40V
mV
Error Amp
Transconductance
ICOMP = −30 μA to +30 μA
VCOMP = 1.0V
1.193
260
0.678
2.259
mmho
V/V
AVOL
Error Amp
Voltage Gain
VCOMP = 0.5V to 1.6V
151/75
RCOMP = 1.0 MΩ(3)
(1) External components such as the diode, inductor, input and output capacitors can affect switching regulator performance. When the
LM2587 is used as shown in Figure 7 and Figure 8, system performance will be as specified by the system parameters.
(2) All room temperature limits are 100% production tested, and all limits at temperature extremes are specified via correlation using
standard Statistical Quality Control (SQC) methods.
(3) A 1.0 MΩ resistor is connected to the compensation pin (which is the error amplifier output) to ensure accuracy in measuring AVOL
.
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LM2587-5.0 Electrical Characteristics
Specifications with standard type face are for TJ = 25°C, and those in bold type face apply over full Operating Temperature
Range. Unless otherwise specified, VIN = 5V.
Symbol
Parameters
Conditions
Typical
Min
Max
Units
SYSTEM PARAMETERS Test Circuit of Figure 7(1)
VOUT
Output Voltage
Line Regulation
Load Regulation
Efficiency
VIN = 4V to 12V
ILOAD = 500 mA to 1.45A
5.0
20
20
80
4.80/4.75
5.20/5.25
50/100
V
ΔVOUT
ΔVIN
/
/
VIN = 4V to 12V
ILOAD = 500 mA
mV
mV
%
ΔVOUT
ΔILOAD
VIN = 12V
ILOAD = 500 mA to 1.45A
50/100
η
VIN = 12V, ILOAD = 750 mA
UNIQUE DEVICE PARAMETERS(2)
VREF
ΔVREF
GM
Output Reference
Voltage
Measured at Feedback Pin
VCOMP = 1.0V
5.0
3.3
4.913/4.900
5.088/5.100
V
Reference Voltage
Line Regulation
VIN = 4V to 40V
mV
Error Amp
Transconductance
ICOMP = −30 μA to +30 μA
VCOMP = 1.0V
0.750
165
0.447
1.491
mmho
V/V
AVOL
Error Amp
Voltage Gain
VCOMP = 0.5V to 1.6V
99/49
RCOMP = 1.0 MΩ(3)
(1) External components such as the diode, inductor, input and output capacitors can affect switching regulator performance. When the
LM2587 is used as shown in Figure 7 and Figure 8, system performance will be as specified by the system parameters.
(2) All room temperature limits are 100% production tested, and all limits at temperature extremes are specified via correlation using
standard Statistical Quality Control (SQC) methods.
(3) A 1.0 MΩ resistor is connected to the compensation pin (which is the error amplifier output) to ensure accuracy in measuring AVOL
.
LM2587-12 Electrical Characteristics
Specifications with standard type face are for TJ = 25°C, and those in bold type face apply over full Operating Temperature
Range. Unless otherwise specified, VIN = 5V.
Symbol
Parameters
Conditions
Typical
Min
Max
Units
SYSTEM PARAMETERS Test Circuit of Figure 8(1)
VOUT
Output Voltage
Line Regulation
Load Regulation
Efficiency
VIN = 4V to 10V
ILOAD = 300 mA to 1.2A
12.0
20
11.52/11.40
12.48/12.60
100/200
V
ΔVOUT
ΔVIN
/
/
VIN = 4V to 10V
ILOAD = 300 mA
mV
mV
%
ΔVOUT
ΔILOAD
VIN = 10V
ILOAD = 300 mA to 1.2A
20
100/200
η
VIN = 10V, ILOAD = 1A
90
UNIQUE DEVICE PARAMETERS(2)
VREF
ΔVREF
GM
Output Reference
Voltage
Measured at Feedback Pin
VCOMP = 1.0V
12.0
7.8
11.79/11.76
12.21/12.24
V
Reference Voltage
Line Regulation
VIN = 4V to 40
mV
Error Amp
Transconductance
ICOMP = −30 μA to +30 μA
VCOMP = 1.0V
0.328
70
0.186
0.621
mmho
V/V
AVOL
Error Amp
Voltage Gain
VCOMP = 0.5V to 1.6V
41/21
RCOMP = 1.0 MΩ(3)
(1) External components such as the diode, inductor, input and output capacitors can affect switching regulator performance. When the
LM2587 is used as shown in Figure 7 and Figure 8, system performance will be as specified by the system parameters.
(2) All room temperature limits are 100% production tested, and all limits at temperature extremes are specified via correlation using
standard Statistical Quality Control (SQC) methods.
(3) A 1.0 MΩ resistor is connected to the compensation pin (which is the error amplifier output) to ensure accuracy in measuring AVOL
.
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LM2587-ADJ Electrical Characteristics
Specifications with standard type face are for TJ = 25°C, and those in bold type face apply over full Operating Temperature
Range. Unless otherwise specified, VIN = 5V.
Symbol
Parameters
Conditions
Typical
Min
Max
Units
SYSTEM PARAMETERS Test Circuit of Figure 8(1)
VOUT
Output Voltage
Line Regulation
Load Regulation
Efficiency
VIN = 4V to 10V
ILOAD = 300 mA to 1.2A
12.0
20
11.52/11.40
12.48/12.60
100/200
V
ΔVOUT
ΔVIN
/
/
VIN = 4V to 10V
ILOAD = 300 mA
mV
mV
%
ΔVOUT
ΔILOAD
VIN = 10V
ILOAD = 300 mA to 1.2A
20
100/200
η
VIN = 10V, ILOAD = 1A
90
UNIQUE DEVICE PARAMETERS(2)
VREF
ΔVREF
GM
Output Reference
Voltage
Measured at Feedback Pin
VCOMP = 1.0V
1.230
1.5
1.208/1.205
1.252/1.255
6.000
V
mV
Reference Voltage
Line Regulation
VIN = 4V to 40V
Error Amp
Transconductance
ICOMP = −30 μA to +30 μA
VCOMP = 1.0V
3.200
670
1.800
mmho
V/V
nA
AVOL
IB
Error Amp
Voltage Gain
VCOMP = 0.5V to 1.6V
400/200
RCOMP = 1.0 MΩ(3)
Error Amp
VCOMP = 1.0V
125
425/600
Input Bias Current
(1) External components such as the diode, inductor, input and output capacitors can affect switching regulator performance. When the
LM2587 is used as shown in Figure 7 and Figure 8, system performance will be as specified by the system parameters.
(2) All room temperature limits are 100% production tested, and all limits at temperature extremes are specified via correlation using
standard Statistical Quality Control (SQC) methods.
(3) A 1.0 MΩ resistor is connected to the compensation pin (which is the error amplifier output) to ensure accuracy in measuring AVOL
.
All Output Voltage Versions Electrical Characteristics(1)
Specifications with standard type face are for TJ = 25°C, and those in bold type face apply over full Operating Temperature
Range. Unless otherwise specified, VIN = 5V.
Symbol
IS
Parameters
Conditions
Typical
Min
Max
Units
Input Supply Current
(Switch Off)
See(2)
11
15.5/16.5
mA
ISWITCH = 3.0A
85
140/165
mA
V
VUV
fO
Input Supply
Undervoltage Lockout
RLOAD = 100Ω
3.30
3.05
3.75
Oscillator Frequency
Measured at Switch Pin
RLOAD = 100Ω
100
85/75
115/125
kHz
VCOMP = 1.0V
fSC
Short-Circuit
Frequency
Measured at Switch Pin
RLOAD = 100Ω
25
2.8
kHz
V
VFEEDBACK = 1.15V
VEAO
Error Amplifier
Output Swing
Upper Limit
See(3)
2.6/2.4
110/70
Lower Limit
See(2)
See(4)
0.25
0.40/0.55
260/320
V
IEAO
Error Amp
Output Current
(Source or Sink)
165
μA
(1) All room temperature limits are 100% production tested, and all limits at temperature extremes are specified via correlation using
standard Statistical Quality Control (SQC) methods.
(2) To measure this parameter, the feedback voltage is set to a high value, depending on the output version of the device, to force the error
amplifier output low. Adj: VFB = 1.41V; 3.3V: VFB = 3.80V; 5.0V: VFB = 5.75V; 12V: VFB = 13.80V.
(3) To measure this parameter, the feedback voltage is set to a low value, depending on the output version of the device, to force the error
amplifier output high. Adj: VFB = 1.05V; 3.3V: VFB = 2.81V; 5.0V: VFB = 4.25V; 12V: VFB = 10.20V.
(4) To measure the worst-case error amplifier output current, the LM2587 is tested with the feedback voltage set to its low value (specified
in Note 7) and at its high value (specified in Note 8).
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All Output Voltage Versions Electrical Characteristics(1) (continued)
Specifications with standard type face are for TJ = 25°C, and those in bold type face apply over full Operating Temperature
Range. Unless otherwise specified, VIN = 5V.
Symbol
ISS
Parameters
Conditions
Typical
Min
Max
Units
Soft Start Current
VFEEDBACK = 0.92V
VCOMP = 1.0V
11.0
8.0/7.0
17.0/19.0
μA
D
Maximum Duty Cycle
RLOAD = 100Ω
98
15
93/90
65
%
μA
V
See(3)
IL
Switch Leakage
Current
Switch Off
VSWITCH = 60V
300/600
VSUS
VSAT
ICL
Switch Sustaining
Voltage
dV/dT = 1.5V/ns
ISWITCH = 5.0A
Switch Saturation
Voltage
0.7
6.5
1.1/1.4
V
NPN Switch
Current Limit
5.0
9.5
A
COMMON DEVICE PARAMETERS(5)
θJA
θJA
θJC
θJA
θJA
θJA
θJC
Thermal Resistance
NDH Package, Junction to Ambient(6)
NDH Package, Junction to Ambient(7)
NDH Package, Junction to Case
KTT Package, Junction to Ambient(8)
KTT Package, Junction to Ambient(9)
KTT Package, Junction to Ambient(10)
KTT Package, Junction to Case
65
45
2
°C/W
56
35
26
2
(5) External components such as the diode, inductor, input and output capacitors can affect switching regulator performance. When the
LM2587 is used as shown in Figure 7 and Figure 8, system performance will be as specified by the system parameters.
(6) Junction to ambient thermal resistance (no external heat sink) for the 5 lead TO-220 package mounted vertically, with ½ inch leads in a
socket, or on a PC board with minimum copper area.
(7) Junction to ambient thermal resistance (no external heat sink) for the 5 lead TO-220 package mounted vertically, with ½ inch leads
soldered to a PC board containing approximately 4 square inches of (1oz.) copper area surrounding the leads.
(8) Junction to ambient thermal resistance for the 5 lead TO-263 mounted horizontally against a PC board area of 0.136 square inches (the
same size as the TO-263 package) of 1 oz. (0.0014 in. thick) copper.
(9) Junction to ambient thermal resistance for the 5 lead TO-263 mounted horizontally against a PC board area of 0.4896 square inches
(3.6 times the area of the TO-263 package) of 1 oz. (0.0014 in. thick) copper.
(10) Junction to ambient thermal resistance for the 5 lead TO-263 mounted horizontally against a PC board copper area of 1.0064 square
inches (7.4 times the area of the TO-263 package) of 1 oz. (0.0014 in. thick) copper. Additional copper area will reduce thermal
resistance further. See the thermal model in Switchers Made Simple® software.
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Typical Performance Characteristics
Supply Current
vs Temperature
Reference Voltage
vs Temperature
Figure 10.
Figure 11.
ΔReference Voltage
vs Supply Voltage
Supply Current
vs Switch Current
Figure 12.
Figure 13.
Current Limit
vs Temperature
Feedback Pin Bias
Current vs Temperature
Figure 14.
Figure 15.
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Typical Performance Characteristics (continued)
Switch Saturation
Voltage vs Temperature
Switch Transconductance
vs Temperature
Figure 16.
Figure 17.
Oscillator Frequency
vs Temperature
Error Amp Transconductance
vs Temperature
Figure 18.
Figure 19.
Error Amp Voltage
Gain vs Temperature
Short Circuit Frequency
vs Temperature
Figure 20.
Figure 21.
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Performance Characteristics
A: Switch Voltage, 10 V/divB: Switch Current, 5 A/divC: Output Rectifier Current, 5 A/divD: Output Ripple Voltage, 100 mV/div
AC-Coupled
Horizontal: 2 μs/div
Figure 22. Switching Waveforms
Figure 23. VOUT Load Current Step Response
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TYPICAL FLYBACK REGULATOR APPLICATIONS
Figure 24 Figure 25 Figure 26 Figure 27 Figure 28 show six typical flyback applications, varying from single
output to triple output. Each drawing contains the part number(s) and manufacturer(s) for every component
except the transformer. For the transformer part numbers and manufacturers names, see the table in
TRANSFORMER SELECTION (T). For applications with different output voltages—requiring the LM2587-
ADJ—or different output configurations that do not match the standard configurations, refer to the Switchers
Made Simple software.
Figure 24. Single-Output Flyback Regulator
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Figure 25. Single-Output Flyback Regulator
Figure 26. Single-Output Flyback Regulator
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Figure 27. Dual-Output Flyback Regulator
Figure 28. Dual-Output Flyback Regulator
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Figure 29. Triple-Output Flyback Regulator
TRANSFORMER SELECTION (T)
Table 1 lists the standard transformers available for flyback regulator applications. Included in the table are the
turns ratio(s) for each transformer, as well as the output voltages, input voltage ranges, and the maximum load
currents for each circuit.
Table 1. Transformer Selection Table
Applications
Transformers
VIN
Figure 24
T1
Figure 25
T1
Figure 26
T1
Figure 27
T2
Figure 28
T3
Figure 29
T4
4V–6V
3.3V
1.8A
1
4V–6V
5V
8V–16V
12V
4V–6V
12V
18V–36V
12V
18V–36V
5V
VOUT1
IOUT1 (Max)
N1
1.4A
1
1.2A
0.3A
2.5
1A
2.5A
0.35
1
0.8
VOUT2
−12V
0.3A
2.5
−12V
1A
12V
IOUT2 (Max)
N2
0.5A
0.8
0.8
VOUT3
−12V
0.5A
0.8
IOUT3 (Max)
N3
Table 2. Transformer Manufacturer Guide
Transformer
Type
Manufacturers' Part Numbers
(1)
(2)
Coilcraft(1)
Coilcraft
Pulse
Renco(3)
Schott(4)
Surface Mount
Q4435-B
Q4436-B
—
Surface Mount
PE-68411
T1
T2
T3
Q4434-B
Q4337-B
Q4343-B
RL-5530
RL-5531
RL-5534
67141450
67140860
67140920
PE-68412
PE-68421
(1) Coilcraft Inc.,: Phone: (800) 322-26451102 Silver Lake Road, Cary, IL 60013: Fax: (708) 639-1469
(2) Pulse Engineering Inc.,: Phone: (619) 674-810012220 World Trade Drive, San Diego, CA 92128: Fax: (619) 674-8262
(3) Renco Electronics Inc.,: Phone: (800) 645-582860 Jeffryn Blvd. East, Deer Park, NY 11729: Fax: (516) 586-5562
(4) Schott Corp.,: Phone: (612) 475-11731000 Parkers Lane Road, Wayzata, MN 55391: Fax: (612) 475-1786
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Table 2. Transformer Manufacturer Guide (continued)
Transformer
Type
Manufacturers' Part Numbers
(1)
(2)
Coilcraft(1)
Coilcraft
Pulse
Renco(3)
Schott(4)
Surface Mount
Surface Mount
T4
Q4344-B
—
PE-68422
RL-5535
67140930
TRANSFORMER FOOTPRINTS
Figure 30, Figure 31, Figure 32, Figure 33, Figure 34, Figure 35, Figure 36, Figure 37, Figure 38 Figure 39,
Figure 40, Figure 41, Figure 42, Figure 43, Figure 44, Figure 45, Figure 46, and Figure 47 show the footprints of
each transformer, listed in Table 1.
T1
T2
Figure 30. Coilcraft Q4434-B (Top View)
Figure 31. Coilcraft Q4337-B (Top View)
T3
T4
Figure 32. Coilcraft Q4343-B (Top View)
Figure 33. Coilcraft Q4344-B (Top View)
T1
T2
Figure 34. Coilcraft Q4435-B (Surface Mount) (Top Figure 35. Coilcraft Q4436-B (Surface Mount) (Top
View)
View)
T1
T2
Figure 36. Pulse PE-68411 (Surface Mount) (Top
View)
Figure 37. Pulse PE-68412 (Surface Mount) (Top
View)
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T3
T4
Figure 38. Pulse PE-68421 (Surface Mount) (Top
View)
Figure 39. Pulse PE-68422 (Surface Mount) (Top
View)
T1
T2
Figure 40. Renco RL-5530 (Top View)
Figure 41. Renco RL-5531 (Top View)
T3
T4
Figure 42. Renco RL-5534 (Top View)
Figure 43. Renco RL-5535 (Top View)
T1
T2
Figure 44. Schott 67141450 (Top View)
Figure 45. Schott 67140860 (Top View)
T3
T4
Figure 46. Schott 67140920 (Top View)
Step-Up (Boost) Regulator Operation
Figure 47. Schott 67140930 (Top View)
Figure 48 shows the LM2587 used as a step-up (boost) regulator. This is a switching regulator that produces an
output voltage greater than the input supply voltage.
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A brief explanation of how the LM2587 Boost Regulator works is as follows (refer to Figure 48). When the NPN
switch turns on, the inductor current ramps up at the rate of VIN/L, storing energy in the inductor. When the
switch turns off, the lower end of the inductor flies above VIN, discharging its current through diode (D) into the
output capacitor (COUT) at a rate of (VOUT − VIN)/L. Thus, energy stored in the inductor during the switch on time
is transferred to the output during the switch off time. The output voltage is controlled by adjusting the peak
switch current, as described in the Flyback Regulator Operation section.
By adding a small number of external components (as shown in Figure 48), the LM2587 can be used to produce a
regulated output voltage that is greater than the applied input voltage. The switching waveforms observed during the
operation of this circuit are shown in Figure 49. Typical performance of this regulator is shown in Figure 50.
Figure 48. 12V Boost Regulator
Typical Performance Characteristics
A: Switch Voltage, 10 V/divB: Switch Current, 5 A/divC: Inductor Current, 5 A/divD: Output Ripple Voltage,
100 mV/div, AC-Coupled
Horizontal: 2 μs/div
Figure 49. Switching Waveforms
Figure 50. VOUT Response to Load Current Step
Typical Boost Regulator Applications
Figure 51 and Figure 52 Figure 53 and Figure 54 show four typical boost applications)—one fixed and three
using the adjustable version of the LM2587. Each drawing contains the part number(s) and manufacturer(s) for
every component. For the fixed 12V output application, the part numbers and manufacturers' names for the
inductor are listed in a table in Figure 54. For applications with different output voltages, refer to the Switchers
Made Simple software.
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Figure 51. +5V to +12V Boost Regulator
Table 3 contains a table of standard inductors, by part number and corresponding manufacturer, for the fixed
output regulator of Figure 51.
Table 3. Inductor Selection Table
(1)
(2)
Coilcraft
R4793-A
Pulse
PE-53900
Renco(3)
Schott(4)
RL-5472-5
67146520
(1) Coilcraft Inc.,: Phone: (800) 322-26451102 Silver Lake Road, Cary, IL 60013: Fax: (708) 639-1469
(2) Pulse Engineering Inc.,: Phone: (619) 674-810012220 World Trade Drive, San Diego, CA 92128: Fax: (619) 674-8262
(3) Renco Electronics Inc.,: Phone: (800) 645-582860 Jeffryn Blvd. East, Deer Park, NY 11729: Fax: (516) 586-5562
(4) Schott Corp.,: Phone: (612) 475-11731000 Parkers Lane Road, Wayzata, MN 55391: Fax: (612) 475-1786
Figure 52. +12V to +24V Boost Regulator
Figure 53. +24V to +36V Boost Regulator
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*The LM2587 will require a heat sink in these applications. The size of the heat sink will depend on the maximum
ambient temperature. To calculate the thermal resistance of the IC and the size of the heat sink needed, see the
“Heat Sink/Thermal Considerations” section in Application Hints.
Figure 54. +24V to +48V Boost Regulator
Application Hints
Figure 55. Boost Regulator
PROGRAMMING OUTPUT VOLTAGE
(SELECTING R1 AND R2)
Referring to the adjustable regulator in Figure 55, the output voltage is programmed by the resistors R1 and R2
by the following formula:
VOUT = VREF (1 + R1/R2)
where VREF = 1.23V
(1)
Resistors R1 and R2 divide the output voltage down so that it can be compared with the 1.23V internal reference.
With R2 between 1k and 5k, R1 is:
R1 = R2 (VOUT/VREF − 1)
where VREF = 1.23V
(2)
For best temperature coefficient and stability with time, use 1% metal film resistors.
SHORT CIRCUIT CONDITION
Due to the inherent nature of boost regulators, when the output is shorted (see Figure 55), current flows directly
from the input, through the inductor and the diode, to the output, bypassing the switch. The current limit of the
switch does not limit the output current for the entire circuit. To protect the load and prevent damage to the
switch, the current must be externally limited, either by the input supply or at the output with an external current
limit circuit. The external limit should be set to the maximum switch current of the device, which is 5A.
In a flyback regulator application (Figure 56), using the standard transformers, the LM2587 will survive a short
circuit to the main output. When the output voltage drops to 80% of its nominal value, the frequency will drop to
25 kHz. With a lower frequency, off times are larger. With the longer off times, the transformer can release all of
its stored energy before the switch turns back on. Hence, the switch turns on initially with zero current at its
collector. In this condition, the switch current limit will limit the peak current, saving the device.
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FLYBACK REGULATOR INPUT CAPACITORS
A flyback regulator draws discontinuous pulses of current from the input supply. Therefore, there are two input
capacitors needed in a flyback regulator; one for energy storage and one for filtering (see Figure 56). Both are
required due to the inherent operation of a flyback regulator. To keep a stable or constant voltage supply to the
LM2587, a storage capacitor (≥100 μF) is required. If the input source is a recitified DC supply and/or the
application has a wide temperature range, the required rms current rating of the capacitor might be very large.
This means a larger value of capacitance or a higher voltage rating will be needed of the input capacitor. The
storage capacitor will also attenuate noise which may interfere with other circuits connected to the same input
supply voltage.
Figure 56. Flyback Regulator
In addition, a small bypass capacitor is required due to the noise generated by the input current pulses. To
eliminate the noise, insert a 1.0 μF ceramic capacitor between VIN and ground as close as possible to the device.
SWITCH VOLTAGE LIMITS
In a flyback regulator, the maximum steady-state voltage appearing at the switch, when it is off, is set by the
transformer turns ratio, N, the output voltage, VOUT, and the maximum input voltage, VIN (Max):
VSW(OFF) = VIN (Max) + (VOUT +VF)/N
(3)
where VF is the forward biased voltage of the output diode, and is 0.5V for Schottky diodes and 0.8V for ultra-fast
recovery diodes (typically). In certain circuits, there exists a voltage spike, VLL, superimposed on top of the
steady-state voltage (see Figure 22, waveform A). Usually, this voltage spike is caused by the transformer
leakage inductance and/or the output rectifier recovery time. To “clamp” the voltage at the switch from exceeding
its maximum value, a transient suppressor in series with a diode is inserted across the transformer primary (as
shown in the circuit on the front page and other flyback regulator circuits throughout the datasheet). The
schematic in Figure 56 shows another method of clamping the switch voltage. A single voltage transient
suppressor (the SA51A) is inserted at the switch pin. This method clamps the total voltage across the switch, not
just the voltage across the primary.
If poor circuit layout techniques are used (see the CIRCUIT LAYOUT GUIDELINES section), negative voltage
transients may appear on the Switch pin (pin 4). Applying a negative voltage (with respect to the IC's ground) to
any monolithic IC pin causes erratic and unpredictable operation of that IC. This holds true for the LM2587 IC as
well. When used in a flyback regulator, the voltage at the Switch pin (pin 4) can go negative when the switch
turns on. The “ringing” voltage at the switch pin is caused by the output diode capacitance and the transformer
leakage inductance forming a resonant circuit at the secondary(ies). The resonant circuit generates the “ringing”
voltage, which gets reflected back through the transformer to the switch pin. There are two common methods to
avoid this problem. One is to add an RC snubber around the output rectifier(s), as in Figure 56. The values of the
resistor and the capacitor must be chosen so that the voltage at the Switch pin does not drop below −0.4V. The
resistor may range in value between 10Ω and 1 kΩ, and the capacitor will vary from 0.001 μF to 0.1 μF. Adding a
snubber will (slightly) reduce the efficiency of the overall circuit.
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The other method to reduce or eliminate the “ringing” is to insert a Schottky diode clamp between pins 4 and 3
(ground), also shown in Figure 56. This prevents the voltage at pin 4 from dropping below −0.4V. The reverse
voltage rating of the diode must be greater than the switch off voltage.
Figure 57. Input Line Filter
OUTPUT VOLTAGE LIMITATIONS
The maximum output voltage of a boost regulator is the maximum switch voltage minus a diode drop. In a
flyback regulator, the maximum output voltage is determined by the turns ratio, N, and the duty cycle, D, by the
equation:
VOUT ≈ N × VIN × D/(1 − D)
(4)
The duty cycle of a flyback regulator is determined by the following equation:
(5)
Theoretically, the maximum output voltage can be as large as desired—just keep increasing the turns ratio of the
transformer. However, there exists some physical limitations that prevent the turns ratio, and thus the output
voltage, from increasing to infinity. The physical limitations are capacitances and inductances in the LM2587
switch, the output diode(s), and the transformer—such as reverse recovery time of the output diode (mentioned
above).
NOISY INPUT LINE CONDITION)
A small, low-pass RC filter should be used at the input pin of the LM2587 if the input voltage has an unusual
large amount of transient noise, such as with an input switch that bounces. The circuit in Figure 57 demonstrates
the layout of the filter, with the capacitor placed from the input pin to ground and the resistor placed between the
input supply and the input pin. Note that the values of RIN and CIN shown in the schematic are good enough for
most applications, but some readjusting might be required for a particular application. If efficiency is a major
concern, replace the resistor with a small inductor (say 10 μH and rated at 100 mA).
STABILITY
All current-mode controlled regulators can suffer from an instability, known as subharmonic oscillation, if they
operate with a duty cycle above 50%. To eliminate subharmonic oscillations, a minimum value of inductance is
required to ensure stability for all boost and flyback regulators. The minimum inductance is given by:
(6)
where VSAT is the switch saturation voltage and can be found in the Characteristic Curves.
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Figure 58. Circuit Board Layout
CIRCUIT LAYOUT GUIDELINES
As in any switching regulator, layout is very important. Rapidly switching currents associated with wiring
inductance generate voltage transients which can cause problems. For minimal inductance and ground loops,
keep the length of the leads and traces as short as possible. Use single point grounding or ground plane
construction for best results. Separate the signal grounds from the power grounds (as indicated in Figure 58).
When using the Adjustable version, physically locate the programming resistors as near the regulator IC as
possible, to keep the sensitive feedback wiring short.
HEAT SINK/THERMAL CONSIDERATIONS
In many cases, no heat sink is required to keep the LM2587 junction temperature within the allowed operating
range. For each application, to determine whether or not a heat sink will be required, the following must be
identified:
1) Maximum ambient temperature (in the application).
2) Maximum regulator power dissipation (in the application).
3) Maximum allowed junction temperature (125°C for the LM2587). For a safe, conservative design, a
temperature approximately 15°C cooler than the maximum junction temperature should be selected (110°C).
4) LM2587 package thermal resistances θJA and θJC (given in the Electrical Characteristics).
Total power dissipated (PD) by the LM2587 can be estimated as follows:
Boost:
(7)
VIN is the minimum input voltage, VOUT is the output voltage, N is the transformer turns ratio, D is the duty cycle,
and ILOAD is the maximum load current (and ∑ILOAD is the sum of the maximum load currents for multiple-output
flyback regulators). The duty cycle is given by:
Boost:
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(8)
where VF is the forward biased voltage of the diode and is typically 0.5V for Schottky diodes and 0.8V for fast
recovery diodes. VSAT is the switch saturation voltage and can be found in the Characteristic Curves.
When no heat sink is used, the junction temperature rise is:
ΔTJ = PD × θJA.
(9)
Adding the junction temperature rise to the maximum ambient temperature gives the actual operating junction
temperature:
TJ = ΔTJ + TA.
(10)
If the operating junction temperature exceeds the maximum junction temperatue in item 3 above, then a heat
sink is required. When using a heat sink, the junction temperature rise can be determined by the following:
ΔTJ = PD × (θJC + θInterface + θHeat Sink
)
(11)
Again, the operating junction temperature will be:
TJ = ΔTJ + TA
(12)
As before, if the maximum junction temperature is exceeded, a larger heat sink is required (one that has a lower
thermal resistance).
Included in the Switchers Made Simple design software is a more precise (non-linear) thermal model that can
be used to determine junction temperature with different input-output parameters or different component values.
It can also calculate the heat sink thermal resistance required to maintain the regulator junction temperature
below the maximum operating temperature.
To further simplify the flyback regulator design procedure, TI is making available computer design software.
Switchers Made Simple software is available on a (3½″) diskette for IBM compatible computers from a TI sales
office in your area or the TI WEBENCH Design Center team.
http://www.ti.com/ww/en/analog/webench/index.shtml?DCMP=hpa_sva_webench&HQS=webench-bb
European Magnetic Vendor
Contacts
Please contact the following addresses for details of local distributors or representatives:
Coilcraft
21 Napier Place
Wardpark North Cumbernauld, Scotland G68 0LL Phone: +44 1236 730 595 Fax: +44 1236 730 627
Pulse Engineering
Dunmore Road
Tuam Co. Galway, Ireland Phone: +353 93 24 107 Fax: +353 93 24 459
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SNVS115D –APRIL 2000–REVISED APRIL 2013
REVISION HISTORY
Changes from Revision C (April 2013) to Revision D
Page
•
Changed layout of National Data Sheet to TI format .......................................................................................................... 24
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PACKAGE OPTION ADDENDUM
www.ti.com
1-Nov-2013
PACKAGING INFORMATION
Orderable Device
LM2587S-12/NOPB
LM2587S-3.3/NOPB
LM2587S-5.0
Status Package Type Package Pins Package
Eco Plan
Lead/Ball Finish
MSL Peak Temp
Op Temp (°C)
-40 to 125
-40 to 125
-40 to 125
-40 to 125
-40 to 125
-40 to 125
-40 to 125
-40 to 125
-40 to 125
-40 to 125
-40 to 125
-40 to 125
-40 to 125
-40 to 125
-40 to 125
-40 to 125
Device Marking
Samples
Drawing
Qty
(1)
(2)
(6)
(3)
(4/5)
ACTIVE
DDPAK/
TO-263
KTT
5
5
5
5
5
5
5
5
5
5
5
5
5
5
5
5
45
Pb-Free (RoHS
Exempt)
CU SN
CU SN
Call TI
CU SN
Call TI
CU SN
CU SN
CU SN
Call TI
CU SN
Call TI
CU SN
CU SN
CU SN
Call TI
CU SN
Level-3-245C-168 HR
Level-3-245C-168 HR
Call TI
LM2587S
-12 P+
ACTIVE
NRND
DDPAK/
TO-263
KTT
KTT
KTT
KTT
KTT
KTT
KTT
KTT
KTT
NDH
NDH
NDH
NDH
NDH
NDH
45
45
Pb-Free (RoHS
Exempt)
LM2587S
-3.3 P+
DDPAK/
TO-263
TBD
LM2587S
-5.0 P+
LM2587S-5.0/NOPB
LM2587S-ADJ
ACTIVE
NRND
DDPAK/
TO-263
45
Pb-Free (RoHS
Exempt)
Level-3-245C-168 HR
Call TI
LM2587S
-5.0 P+
DDPAK/
TO-263
45
TBD
LM2587S
-ADJ P+
LM2587S-ADJ/NOPB
LM2587SX-12/NOPB
LM2587SX-5.0/NOPB
LM2587SX-ADJ
ACTIVE
ACTIVE
ACTIVE
NRND
DDPAK/
TO-263
45
Pb-Free (RoHS
Exempt)
Level-3-245C-168 HR
Level-3-245C-168 HR
Level-3-245C-168 HR
Call TI
LM2587S
-ADJ P+
DDPAK/
TO-263
500
500
500
500
45
Pb-Free (RoHS
Exempt)
LM2587S
-12 P+
DDPAK/
TO-263
Pb-Free (RoHS
Exempt)
LM2587S
-5.0 P+
DDPAK/
TO-263
TBD
LM2587S
-ADJ P+
LM2587SX-ADJ/NOPB
LM2587T-12
ACTIVE
NRND
DDPAK/
TO-263
Pb-Free (RoHS
Exempt)
Level-3-245C-168 HR
Call TI
LM2587S
-ADJ P+
TO-220
TO-220
TO-220
TO-220
TO-220
TO-220
TBD
LM2587T
-12 P+
LM2587T-12/NOPB
LM2587T-3.3/NOPB
LM2587T-5.0/NOPB
LM2587T-ADJ
ACTIVE
ACTIVE
ACTIVE
NRND
45
Pb-Free (RoHS
Exempt)
Level-1-NA-UNLIM
Level-1-NA-UNLIM
Level-1-NA-UNLIM
Call TI
LM2587T
-12 P+
45
Pb-Free (RoHS
Exempt)
LM2587T
-3.3 P+
45
Pb-Free (RoHS
Exempt)
LM2587T
-5.0 P+
45
TBD
LM2587T
-ADJ P+
LM2587T-ADJ/NOPB
ACTIVE
45
Pb-Free (RoHS
Exempt)
Level-1-NA-UNLIM
LM2587T
-ADJ P+
(1) The marketing status values are defined as follows:
ACTIVE: Product device recommended for new designs.
Addendum-Page 1
PACKAGE OPTION ADDENDUM
www.ti.com
1-Nov-2013
LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect.
NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in a new design.
PREVIEW: Device has been announced but is not in production. Samples may or may not be available.
OBSOLETE: TI has discontinued the production of the device.
(2) Eco Plan - The planned eco-friendly classification: Pb-Free (RoHS), Pb-Free (RoHS Exempt), or Green (RoHS & no Sb/Br) - please check http://www.ti.com/productcontent for the latest availability
information and additional product content details.
TBD: The Pb-Free/Green conversion plan has not been defined.
Pb-Free (RoHS): TI's terms "Lead-Free" or "Pb-Free" mean semiconductor products that are compatible with the current RoHS requirements for all 6 substances, including the requirement that
lead not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered at high temperatures, TI Pb-Free products are suitable for use in specified lead-free processes.
Pb-Free (RoHS Exempt): This component has a RoHS exemption for either 1) lead-based flip-chip solder bumps used between the die and package, or 2) lead-based die adhesive used between
the die and leadframe. The component is otherwise considered Pb-Free (RoHS compatible) as defined above.
Green (RoHS & no Sb/Br): TI defines "Green" to mean Pb-Free (RoHS compatible), and free of Bromine (Br) and Antimony (Sb) based flame retardants (Br or Sb do not exceed 0.1% by weight
in homogeneous material)
(3) MSL, Peak Temp. - The Moisture Sensitivity Level rating according to the JEDEC industry standard classifications, and peak solder temperature.
(4) There may be additional marking, which relates to the logo, the lot trace code information, or the environmental category on the device.
(5) Multiple Device Markings will be inside parentheses. Only one Device Marking contained in parentheses and separated by a "~" will appear on a device. If a line is indented then it is a continuation
of the previous line and the two combined represent the entire Device Marking for that device.
(6) Lead/Ball Finish - Orderable Devices may have multiple material finish options. Finish options are separated by a vertical ruled line. Lead/Ball Finish values may wrap to two lines if the finish
value exceeds the maximum column width.
Important Information and Disclaimer:The information provided on this page represents TI's knowledge and belief as of the date that it is provided. TI bases its knowledge and belief on information
provided by third parties, and makes no representation or warranty as to the accuracy of such information. Efforts are underway to better integrate information from third parties. TI has taken and
continues to take reasonable steps to provide representative and accurate information but may not have conducted destructive testing or chemical analysis on incoming materials and chemicals.
TI and TI suppliers consider certain information to be proprietary, and thus CAS numbers and other limited information may not be available for release.
In no event shall TI's liability arising out of such information exceed the total purchase price of the TI part(s) at issue in this document sold by TI to Customer on an annual basis.
Addendum-Page 2
PACKAGE MATERIALS INFORMATION
www.ti.com
23-Sep-2013
TAPE AND REEL INFORMATION
*All dimensions are nominal
Device
Package Package Pins
Type Drawing
SPQ
Reel
Reel
A0
B0
K0
P1
W
Pin1
Diameter Width (mm) (mm) (mm) (mm) (mm) Quadrant
(mm) W1 (mm)
LM2587SX-12/NOPB
LM2587SX-5.0/NOPB
LM2587SX-ADJ
DDPAK/
TO-263
KTT
KTT
KTT
KTT
5
5
5
5
500
500
500
500
330.0
330.0
330.0
330.0
24.4
24.4
24.4
24.4
10.75 14.85
10.75 14.85
10.75 14.85
10.75 14.85
5.0
5.0
5.0
5.0
16.0
16.0
16.0
16.0
24.0
24.0
24.0
24.0
Q2
Q2
Q2
Q2
DDPAK/
TO-263
DDPAK/
TO-263
LM2587SX-ADJ/NOPB DDPAK/
TO-263
Pack Materials-Page 1
PACKAGE MATERIALS INFORMATION
www.ti.com
23-Sep-2013
*All dimensions are nominal
Device
Package Type Package Drawing Pins
SPQ
Length (mm) Width (mm) Height (mm)
LM2587SX-12/NOPB
LM2587SX-5.0/NOPB
LM2587SX-ADJ
DDPAK/TO-263
DDPAK/TO-263
DDPAK/TO-263
DDPAK/TO-263
KTT
KTT
KTT
KTT
5
5
5
5
500
500
500
500
367.0
367.0
367.0
367.0
367.0
367.0
367.0
367.0
45.0
45.0
45.0
45.0
LM2587SX-ADJ/NOPB
Pack Materials-Page 2
MECHANICAL DATA
NDH0005D
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MECHANICAL DATA
KTT0005B
TS5B (Rev D)
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