LM2651MTCX-ADJ
更新时间：2024-09-18 19:09:35
品牌：TI
描述：2.6A SWITCHING REGULATOR, 345kHz SWITCHING FREQ-MAX, PDSO16, TSSOP-16
概述
规格参数
数据手册
替代型号LM2651MTCX-ADJ 概述
2.6A SWITCHING REGULATOR, 345kHz SWITCHING FREQ-MAX, PDSO16, TSSOP-16 DC/DC转换器 开关式稳压器或控制器
LM2651MTCX-ADJ 规格参数
| 是否无铅： | 含铅 | 是否Rohs认证： | 不符合 |
| 生命周期： | Obsolete | 零件包装代码： | TSSOP |
| 包装说明： | TSSOP, TSSOP16,.25 | 针数： | 16 |
| Reach Compliance Code： | not_compliant | ECCN代码： | EAR99 |
| HTS代码： | 8542.39.00.01 | 风险等级： | 5.11 |
| 模拟集成电路 - 其他类型： | SWITCHING REGULATOR | 控制模式： | CURRENT-MODE |
| 控制技术： | PULSE WIDTH MODULATION | 最大输入电压： | 14 V |
| 最小输入电压： | 4 V | 标称输入电压： | 10 V |
| JESD-30 代码： | R-PDSO-G16 | JESD-609代码： | e0 |
| 长度： | 5 mm | 湿度敏感等级： | 1 |
| 功能数量： | 1 | 端子数量： | 16 |
| 最高工作温度： | 125 °C | 最低工作温度： | -40 °C |
| 最大输出电流： | 2.6 A | 封装主体材料： | PLASTIC/EPOXY |
| 封装代码： | TSSOP | 封装等效代码： | TSSOP16,.25 |
| 封装形状： | RECTANGULAR | 封装形式： | SMALL OUTLINE, THIN PROFILE, SHRINK PITCH |
| 峰值回流温度（摄氏度）： | 260 | 认证状态： | Not Qualified |
| 座面最大高度： | 1.2 mm | 子类别： | Switching Regulator or Controllers |
| 表面贴装： | YES | 切换器配置： | SINGLE |
| 最大切换频率： | 345 kHz | 技术： | CMOS |
| 温度等级： | AUTOMOTIVE | 端子面层： | Tin/Lead (Sn/Pb) |
| 端子形式： | GULL WING | 端子节距： | 0.65 mm |
| 端子位置： | DUAL | 处于峰值回流温度下的最长时间： | NOT SPECIFIED |
| 宽度： | 4.4 mm | Base Number Matches： | 1 |
LM2651MTCX-ADJ 数据手册
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SNVS032D –FEBRUARY 2000–REVISED APRIL 2013
LM2651 1.5A High Efficiency Synchronous Switching Regulator
Check for Samples: LM2651
1
FEATURES
DESCRIPTION
The LM2651 switching regulator provides high
efficiency power conversion over a 100:1 load range
(1.5A to 15mA). This feature makes the LM2651 an
ideal fit in battery-powered applications that demand
long battery life in both run and standby modes.
2
•
•
Ultra High Efficiency up to 97%
High Efficiency Over a 1.5A to Milliamperes
Load Range
•
•
•
4V to 14V Input Voltage Range
1.8V, 2.5V, 3.3V, or ADJ Output Voltage
Synchronous rectification is used to achieve up to
97% efficiency. At light loads, the LM2651 enters a
low power hysteretic or “sleep” mode to keep the
efficiency high. In many applications, the efficiency
still exceeds 80% at 15mA load. A shutdown pin is
available to disable the LM2651 and reduce the
supply current to less than 10µA.
Internal MOSFET Switch with Low RDS(on) of
75mΩ
•
•
•
300kHz Fixed Frequency Internal Oscillator
7µA Shutdown Current
Patented Current Sensing for Current Mode
Control
The LM2651 contains a patented current sensing
circuitry for current mode control. This feature
eliminates the external current sensing resistor
required by other current-mode DC-DC converters.
•
•
•
•
Input Undervoltage Lockout
Adjustable Soft-Start
Current Limit and Thermal Shutdown
16-pin TSSOP Package
The LM2651 has a 300 kHz fixed frequency internal
oscillator. The high oscillator frequency allows the
use of extremely small, low profile components.
APPLICATIONS
A
programmable soft-start feature limits current
•
•
•
•
•
Personal Digital Assistants (PDAs)
Computer Peripherals
surges from the input power supply at start up and
provides a simple means of sequencing multiple
power supplies.
Battery-Powered Devices
Handheld Scanners
Other protection features include input undervoltage
lockout, current limiting, and thermal shutdown.
High Efficiency 5V Conversion
Typical Application
Figure 1. Efficiency vs Load Current
(VIN = 5V, VOUT = 3.3V)
Figure 2.
1
Please be aware that an important notice concerning availability, standard warranty, and use in critical applications of
Texas Instruments semiconductor products and disclaimers thereto appears at the end of this data sheet.
All trademarks are the property of their respective owners.
2
PRODUCTION DATA information is current as of publication date.
Products conform to specifications per the terms of the Texas
Instruments standard warranty. Production processing does not
necessarily include testing of all parameters.
Copyright © 2000–2013, Texas Instruments Incorporated
LM2651
SNVS032D –FEBRUARY 2000–REVISED APRIL 2013
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Connection Diagram
Figure 3. 16-Lead TSSOP
See Package Number PW
PIN DESCRIPTIONS
Pin
1, 2
3-5
6
Name
SW
Function
Switched-node connection, which is connected with the source of the internal high-side MOSFET.
Main power supply pin.
VIN
VCB
Bootstrap capacitor connection for high-side gate drive.
Input supply voltage for control and driver circuits.
7
AVIN
SD(SS)
8
Shutdown and Soft-start control pin. Pulling this pin below 0.3V shuts off the regulator. A capacitor
connected from this pin to ground provides a control ramp of the input current. Do not drive this pin
with an external source or erroneous operation may result.
9
FB
Output voltage feedback input. Connected to the output voltage.
10
COMP
NC
Compensation network connection. Connected to the output of the voltage error amplifier.
11
No internal connection.
Low-noise analog ground.
Power ground.
12-13
14-16
AGND
PGND
These devices have limited built-in ESD protection. The leads should be shorted together or the device placed in conductive foam
during storage or handling to prevent electrostatic damage to the MOS gates.
(1)(2)
Absolute Maximum Ratings
Input Voltage
15V
−0.4V ≤ VFB ≤ 5V
893 mW
Feedback Pin Voltage
Power Dissipation (TA =25°C),
Junction Temperature Range
Storage Temperature Range
ESD Susceptibility
(3)
−40°C ≤ TJ ≤ +125°C
−65°C to +150°C
1kV
(4)
Human Body Model
(1) Absolute maximum ratings indicate limits beyond which damage to the device may occur. Operating ratings indicate conditions for which
the device is intended to be functional, but device parameter specifications may not be ensured under these conditions. For
specifications and test conditions, see the Electrical Characteristics.
(2) If Military/Aerospace specified devices are required, please contact the TI Sales Office/ Distributors for availability and specifications.
(3) The maximum allowable power dissipation is calculated by using PDmax = (TJmax − TA)/θJA , where TJmax is the maximum junction
temperature, TA is the ambient temperature, and θJA is the junction-to-ambient thermal resistance of the specified package. The 893
mW rating results from using 150°C, 25°C, and 140°C/W for TJmax, TA, and θJA respectively. A θJA of 140°C/W represents the worst-
case condition of no heat sinking of the 16-pin TSSOP package. Heat sinking allows the safe dissipation of more power. The Absolute
Maximum power dissipation must be derated by 7.14mW per °C above 25°C ambient. The LM2651 actively limits its junction
temperature to about 165°C.
(4) The human body model is a 100pF capacitor discharged through a 1.5kΩ resistor into each pin.
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(1)
Operating Ratings
Supply Voltage
4V ≤ VIN ≤ 14V
(1) Absolute maximum ratings indicate limits beyond which damage to the device may occur. Operating ratings indicate conditions for which
the device is intended to be functional, but device parameter specifications may not be ensured under these conditions. For
specifications and test conditions, see the Electrical Characteristics.
LM2651-1.8 System Parameters
Specifications in standard type face are for TJ = 25°C and those with boldface type apply over full operating junction
temperature range. VIN =10V unless otherwise specified.
Symbol
VOUT
Parameter
Output Voltage
Conditions
ILOAD = 900 mA
Typical
Limit
Units
1.8
1.761/1.719
1.836/1.854
V
V(min)
V(max)
VOUT
VOUT
VOUT
VHYST
Output Voltage Line Regulation
VIN = 4V to 14V
ILOAD = 900 mA
0.2
1.3
0.3
35
%
Output Voltage Load Regulation ILOAD = 10 mA to 1.5A
VIN = 5V
%
Output Voltage Load Regulation ILOAD = 200 mA to 1.5A
VIN = 5V
%
Sleep Mode Output Voltage
Hysteresis
mV
LM2651-2.5 System Parameters
Symbol
Parameter
Conditions
ILOAD = 900 mA
Typical
Limit
Units
VOUT
Output Voltage
2.5
V
2.43/2.388
2.574/2.575
V(min)
V(max)
VOUT
VOUT
VOUT
VHYST
Output Voltage Line Regulation
VIN = 4V to 12V
ILOAD = 900 mA
0.2
1.3
0.3
48
%
Output Voltage Load Regulation ILOAD = 10 mA to 1.5A
VIN = 5V
%
Output Voltage Load Regulation ILOAD = 200 mA to 1.5A
VIN = 5V
%
Sleep Mode Output Voltage
Hysteresis
mV
LM2651-3.3 System Parameters
Symbol
Parameter
Conditions
ILOAD = 900 mA
Typical
Limit
Units
VOUT
Output Voltage
3.3
V
3.265/3.201
3.379/3.399
V(min)
V(max)
VOUT
VOUT
VOUT
VHYST
Output Voltage Line Regulation
VIN = 4V to 14V
ILOAD = 900 mA
0.2
1.3
0.3
60
%
Output Voltage Load Regulation ILOAD = 10 mA to 1.5A
VIN = 5V
%
Output Voltage Load Regulation ILOAD = 200 mA to 1.5A
VIN = 5V
%
Sleep Mode Output Voltage
Hysteresis
mV
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Units
LM2651-ADJ System Parameters
(VOUT = 2.5V unless otherwise specified)
Symbol
VFB
Parameter
Feedback Voltage
Conditions
ILOAD = 900 mA
Typical
Limit
1.238
V
1.200
1.263
V(min)
V(max)
VOUT
VOUT
VOUT
VHYST
Output Voltage Line Regulation
VIN = 4V to 14V
ILOAD = 900 mA
0.2
1.3
0.3
24
%
Output Voltage Load Regulation ILOAD = 10 mA to 1.5A
VIN = 5V
%
Output Voltage Load Regulation ILOAD = 200 mA to 1.5A
VIN = 5V
%
Sleep Mode Output Voltage
Hysteresis
mV
All Output Voltage Versions
Specifications in standard type face are for TJ = 25°C and those with boldface type apply over full operating junction
temperature range. VIN =10V unless otherwise specified.
Symbol
Parameter
Quiescent Current
Conditions
Typical
Limit
Units
IQ
1.6
mA
mA(max)
2.0
IQSD
Quiescent Current in Shutdown
Mode
Shutdown Pin Pulled Low
ISWITCH = 1A
7
µA
µA(max)
12/20
RSW(ON)
High-Side or Low-Side Switch
On Resistance (MOSFET On
Resistance + Bonding Wire
Resistance)
110
mΩ
RDS(ON)
IL
MOSFET On Resistance (High-
Side or Low-Side)
ISWITCH = 1A
75
mΩ
mΩ(max)
130
Switch Leakage Current - High
Side
130
130
6.75
nA
Switch Leakage Current - Low
Side
nA
VBOOT
Bootstrap Regulator Voltage
IBOOT = 1 mA
V
6.45/6.40
6.95/7.00
V(min)
V(max)
GM
Error Amplifier
Transconductance
1250
3.8
210
2
µmho
VINUV
VUV-HYST
ICL
VIN Undervoltage Lockout
Threshold Voltage
Rising Edge
3.95
V
V(max)
Hysteresis for the Undervoltage
Lockout
mV
Switch Current Limit
VIN = 5V
VIN = 5V
A
1.55
2.60
A(min)
A(max)
ISM
Sleep Mode Threshold Current
Error Amplifier Voltage Gain
Error Amplifier Source Current
100
100
40
mA
V/V
AV
IEA_SOURCE
µA
25/15
30
µA(min)
IEA_SINK
VEAH
VEAL
VD
Error Amplifier Sink Current
65
2.70
1.25
1
µA
µA(min)
Error Amplifier Output Swing
Upper Limit
V
2.50/2.40
1.35/1.50
V(min)
Error Amplifier Output Swing
Lower Limit
V
V(max)
Body Diode Voltage
IDIODE = 1.5A
V
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All Output Voltage Versions (continued)
Specifications in standard type face are for TJ = 25°C and those with boldface type apply over full operating junction
temperature range. VIN =10V unless otherwise specified.
Symbol
fOSC
Parameter
Conditions
Typical
Limit
Units
Oscillator Frequency
VIN = 4V
VIN = 4V
300
kHz
kHz(min)
kHz(max)
280/255
330/345
DMAX
ISS
Maximum Duty Cycle
Soft-Start Current
95
11
%
%(min)
92
Voltage at the SS pin = 1.4V
Shutdown Pin Pulled Low
µA
µA(min)
µA(max)
7
14
ISHUTDOWN
Shutdown Pin Current
2.2
0.6
µA
µA(min)
µA(max)
0.8/0.5
3.7/4.0
vSHUTDOWN
Shutdown Pin Threshold Voltage Falling Edge
Thermal Shutdown Temperature
V
0.3
0.9
V(min)
V(max)
TSD
165
25
°C
TSD_HYST
Thermal Shutdown Hysteresis
Temperature
°C
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Typical Performance Characteristics
IQ vs Input Voltage
IQSD vs Input Voltage
Figure 4.
Figure 5.
IQSD vs Junction Temperature
Frequency vs Junction Temperature
Figure 6.
Figure 7.
RDS(ON) vs Input Voltage
RDS(ON) vs Junction Temperature
Figure 8.
Figure 9.
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Typical Performance Characteristics (continued)
Current Limit vs Input Voltage (VOUT =2.5V)
Current Limit vs Junction Temperature (VOUT =2.5V)
Figure 10.
Current Limit vs Junction Temperature (VOUT = 3.3V)
Figure 11.
Current Limit vs Input Voltage (VOUT = 3.3V)
Figure 12.
Figure 13.
Sleep Mode Threshold vs Output Voltage For ADJ version (VIN = 5V)
Figure 14.
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Figure 15. LM2651 Block Diagram
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SNVS032D –FEBRUARY 2000–REVISED APRIL 2013
BLOCK DIAGRAM
Operation
The LM2651 operates in a constant frequency (300 kHz), current-mode PWM for moderate to heavy loads; and it
automatically switches to hysteretic mode for light loads. In hysteretic mode, the switching frequency is reduced
to keep the efficiency high.
MAIN OPERATION
When the load current is higher than the sleep mode threshold, the part is always operating in PWM mode. At
the beginning of each switching cycle, the high-side switch is turned on, the current from the high-side switch is
sensed and compared with the output of the error amplifier (COMP pin). When the sensed current reaches the
COMP pin voltage level, the high-side switch is turned off; after 40 ns (deadtime), the low-side switch is turned
on. At the end of the switching cycle, the low-side switch is turned off; and the same cycle repeats.
The current of the top switch is sensed by a patented internal circuitry. This unique technique gets rid of the
external sense resistor, saves cost and size, and improves noise immunity of the sensed current. A feedforward
from the input voltage is added to reduce the variation of the current limit over the input voltage range.
When the load current decreases below the sleep mode threshold, the output voltage will rise slightly, this rise is
sensed by the hysteretic mode comparator which makes the part go into the hysteretic mode with both the high
and low side switches off. The output voltage starts to drop until it hits the low threshold of the hysteretic
comparator, and the part immediately goes back to the PWM operation. The output voltage keeps increasing
until it reaches the top hysteretic threshold, then both the high and low side switches turn off again, and the
same cycle repeats.
PROTECTIONS
The cycle-by-cycle current limit circuitry turns off the high-side MOSFET whenever the current in MOSFET
reaches 2A.
Design Procedure
This section presents guidelines for selecting external components.
INPUT CAPACITOR
A low ESR aluminum, tantalum, or ceramic capacitor is needed betwen the input pin and power ground. This
capacitor prevents large voltage transients from appearing at the input. The capacitor is selected based on the
RMS current and voltage requirements. The RMS current is given by:
(1)
The RMS current reaches its maximum (IOUT/2) when VIN equals 2VOUT. For an aluminum or ceramic capacitor,
the voltage rating should be at least 25% higher than the maximum input voltage. If a tantalum capacitor is used,
the voltage rating required is about twice the maximum input voltage. The tantalum capacitor should be surge
current tested by the manufacturer to prevent being shorted by the inrush current. It is also recommended to put
a small ceramic capacitor (0.1 μF) between the input pin and ground pin to reduce high frequency spikes.
INDUCTOR
The most critical parameters for the inductor are the inductance, peak current and the DC resistance. The
inductance is related to the peak-to-peak inductor ripple current, the input and the output voltages:
(2)
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A higher value of ripple current reduces inductance, but increases the conductance loss, core loss, current stress
for the inductor and switch devices. It also requires a bigger output capacitor for the same output voltage ripple
requirement. A reasonable value is setting the ripple current to be 30% of the DC output current. Since the ripple
current increases with the input voltage, the maximum input voltage is always used to determine the inductance.
The DC resistance of the inductor is a key parameter for the efficiency. Lower DC resistance is available with a
bigger winding area. A good tradeoff between the efficiency and the core size is letting the inductor copper loss
equal 2% of the output power.
OUTPUT CAPACITOR
The selection of COUT is driven by the maximum allowable output voltage ripple. The output ripple in the constant
frequency, PWM mode is approximated by:
(3)
The ESR term usually plays the dominant role in determining the voltage ripple. A low ESR aluminum electrolytic
or tantalum capacitor (such as Nichicon PL series, Sanyo OS-CON, Sprague 593D, 594D, AVX TPS, and CDE
polymer aluminum) is recommended. An electrolytic capacitor is not recommended for temperatures below
−25°C since its ESR rises dramatically at cold temperature. A tantalum capacitor has a much better ESR
specification at cold temperature and is preferred for low temperature applications.
The output voltage ripple in constant frequency mode has to be less than the sleep mode voltage hysteresis to
avoid entering the sleep mode at full load:
VRIPPLE < 20mV x VOUT /VFB
(4)
BOOST CAPACITOR
A 0.1 μF ceramic capacitor is recommended for the boost capacitor. The typical voltage across the boost
capacitor is 6.7V.
SOFT-START CAPACITOR
A soft-start capacitor is used to provide the soft-start feature. When the input voltage is first applied, or when the
SD(SS) pin is allowed to go high, the soft-start capacitor is charged by a current source (approximately 2 μA).
When the SD(SS) pin voltage reaches 0.6V (shutdown threshold), the internal regulator circuitry starts to
operate. The current charging the soft-start capacitor increases from 2 μA to approximately 10 μA. With the
SD(SS) pin voltage between 0.6V and 1.3V, the level of the current limit is zero, which means the output voltage
is still zero. When the SD(SS) pin voltage increases beyond 1.3V, the current limit starts to increase. The switch
duty cycle, which is controlled by the level of the current limit, starts with narrow pulses and gradually gets wider.
At the same time, the output voltage of the converter increases towards the nominal value, which brings down
the output voltage of the error amplifier. When the output of the error amplifier is less than the current limit
voltage, it takes over the control of the duty cycle. The converter enters the normal current-mode PWM
operation. The SD(SS) pin voltage is eventually charged up to about 2V.
The soft-start time can be estimated as:
TSS = CSS x 0.6V/2 μA + CSS x (2V−0.6V)/10 μA
(5)
R1 AND R2 (Programming Output Voltage)
Use the following formula to select the appropriate resistor values:
VOUT = VREF(1 + R1/R2)
where
•
VREF = 1.238V
(6)
Select resistors between 10kΩ and 100kΩ. (1% or higher accuracy metal film resistors for R1 and R2.)
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COMPENSATION COMPONENTS
In the control to output transfer function, the first pole Fp1 can be estimated as 1/(2πROUTCOUT); The ESR zero
Fz1 of the output capacitor is 1/(2πESRCOUT); Also, there is a high frequency pole Fp2 in the range of 45kHz to
150kHz:
Fp2 = Fs/(πn(1−D))
where
•
•
D = VOUT/VIN
n = 1+0.348L/(VIN−VOUT) (L is in µHs and VIN and VOUT in volts).
(7)
The total loop gain G is approximately 500/IOUT where IOUT is in amperes.
A Gm amplifier is used inside the LM2651. The output resistor Ro of the Gm amplifier is about 80kΩ. Cc1 and RC
together with Ro give a lag compensation to roll off the gain:
Fpc1 = 1/(2πCc1(Ro+Rc)), Fzc1 = 1/2πCc1Rc.
(8)
In some applications, the ESR zero Fz1 cannot be cancelled by Fp2. Then, Cc2 is needed to introduce Fpc2 to
cancel the ESR zero, Fp2 = 1/(2πCc2Ro‖Rc).
The rule of thumb is to have more than 45° phase margin at the crossover frequency (G=1).
If COUT is higher than 68µF, Cc1 = 2.2nF, and Rc = 15KΩ are good choices for most applications. If the ESR zero
is too low to be cancelled by Fp2, add Cc2.
If the transient response to a step load is important, choose RC to be higher than 10kΩ.
EXTERNAL SCHOTTKY DIODE
A Schottky diode D1 is recommended to prevent the intrinsic body diode of the low-side MOSFET from
conducting during the deadtime in PWM operation and hysteretic mode when both MOSFETs are off. If the body
diode turns on, there is extra power dissipation in the body diode because of the reverse-recovery current and
higher forward voltage; the high-side MOSFET also has more switching loss since the negative diode reverse-
recovery current appears as the high-side MOSFET turn-on current in addition to the load current. These losses
degrade the efficiency by 1-2%. The improved efficiency and noise immunity with the Schottky diode become
more obvious with increasing input voltage and load current.
The breakdown voltage rating of D1 is preferred to be 25% higher than the maximum input voltage. Since D1 is
only on for a short period of time, the average current rating for D1 only requires being higher than 30% of the
maximum output current. It is important to place D1 very close to the drain and source of the low-side MOSFET,
extra parasitic inductance in the parallel loop will slow the turn-on of D1 and direct the current through the body
diode of the low-side MOSFET.
When an undervoltage situation occurs, the output voltage can be pulled below ground as the inductor current is
reversed through the synchronous FET. For applications which need to be protected from a negative voltage, a
clamping diode D2 is recommended. When used, D2 should be connected cathode to VOUT and anode to
ground. A diode rated for a minimum of 2A is recommended.
PCB Layout Considerations
Layout is critical to reduce noises and ensure specified performance. The important guidelines are listed as
follows:
1. Minimize the parasitic inductance in the loop of input capacitors and the internal MOSFETs by connecting the
input capacitors to VIN and PGND pins with short and wide traces. This is important because the rapidly
switching current, together with wiring inductance can generate large voltage spikes that may result in noise
problems.
2. Minimize the trace from the center of the output resistor divider to the FB pin and keep it away from noise
sources to avoid noise pick up. For applications requiring tight regulation at the output, a dedicated sense
trace (separated from the power trace) is recommended to connect the top of the resistor divider to the
output.
3. If the Schottky diode D1 is used, minimize the traces connecting D1 to SW and PGND pins.
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SNVS032D –FEBRUARY 2000–REVISED APRIL 2013
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Figure 16. Schematic for the Typical Board Layout
12
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Copyright © 2000–2013, Texas Instruments Incorporated
Product Folder Links: LM2651
LM2651
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SNVS032D –FEBRUARY 2000–REVISED APRIL 2013
REVISION HISTORY
Changes from Revision C (April 2013) to Revision D
Page
•
Changed layout of National Data Sheet to TI format .......................................................................................................... 11
Copyright © 2000–2013, Texas Instruments Incorporated
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13
Product Folder Links: LM2651
PACKAGE OPTION ADDENDUM
www.ti.com
1-Nov-2013
PACKAGING INFORMATION
Orderable Device
LM2651MTC-3.3
Status Package Type Package Pins Package
Eco Plan
Lead/Ball Finish
MSL Peak Temp
Op Temp (°C)
-40 to 125
-40 to 125
-40 to 125
-40 to 125
-40 to 125
-40 to 125
Device Marking
Samples
Drawing
Qty
(1)
(2)
(6)
(3)
(4/5)
NRND
TSSOP
TSSOP
TSSOP
TSSOP
TSSOP
TSSOP
PW
16
16
16
16
16
16
92
TBD
Call TI
CU SN
Call TI
CU SN
CU SN
CU SN
Call TI
2651MTC
-3.3
LM2651MTC-3.3/NOPB
LM2651MTC-ADJ
ACTIVE
NRND
PW
PW
PW
PW
PW
92
92
Green (RoHS
& no Sb/Br)
Level-1-260C-UNLIM
Call TI
2651MTC
-3.3
TBD
2651MTC
-ADJ
LM2651MTC-ADJ/NOPB
LM2651MTCX-3.3/NOPB
LM2651MTCX-ADJ/NOPB
ACTIVE
ACTIVE
ACTIVE
92
Green (RoHS
& no Sb/Br)
Level-1-260C-UNLIM
Level-1-260C-UNLIM
Level-1-260C-UNLIM
2651MTC
-ADJ
2500
2500
Green (RoHS
& no Sb/Br)
2651MTC
-3.3
Green (RoHS
& no Sb/Br)
2651MTC
-ADJ
(1) The marketing status values are defined as follows:
ACTIVE: Product device recommended for new designs.
LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect.
NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in a new design.
PREVIEW: Device has been announced but is not in production. Samples may or may not be available.
OBSOLETE: TI has discontinued the production of the device.
(2) Eco Plan - The planned eco-friendly classification: Pb-Free (RoHS), Pb-Free (RoHS Exempt), or Green (RoHS & no Sb/Br) - please check http://www.ti.com/productcontent for the latest availability
information and additional product content details.
TBD: The Pb-Free/Green conversion plan has not been defined.
Pb-Free (RoHS): TI's terms "Lead-Free" or "Pb-Free" mean semiconductor products that are compatible with the current RoHS requirements for all 6 substances, including the requirement that
lead not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered at high temperatures, TI Pb-Free products are suitable for use in specified lead-free processes.
Pb-Free (RoHS Exempt): This component has a RoHS exemption for either 1) lead-based flip-chip solder bumps used between the die and package, or 2) lead-based die adhesive used between
the die and leadframe. The component is otherwise considered Pb-Free (RoHS compatible) as defined above.
Green (RoHS & no Sb/Br): TI defines "Green" to mean Pb-Free (RoHS compatible), and free of Bromine (Br) and Antimony (Sb) based flame retardants (Br or Sb do not exceed 0.1% by weight
in homogeneous material)
(3) MSL, Peak Temp. - The Moisture Sensitivity Level rating according to the JEDEC industry standard classifications, and peak solder temperature.
(4) There may be additional marking, which relates to the logo, the lot trace code information, or the environmental category on the device.
(5) Multiple Device Markings will be inside parentheses. Only one Device Marking contained in parentheses and separated by a "~" will appear on a device. If a line is indented then it is a continuation
of the previous line and the two combined represent the entire Device Marking for that device.
Addendum-Page 1
PACKAGE OPTION ADDENDUM
www.ti.com
1-Nov-2013
(6) Lead/Ball Finish - Orderable Devices may have multiple material finish options. Finish options are separated by a vertical ruled line. Lead/Ball Finish values may wrap to two lines if the finish
value exceeds the maximum column width.
Important Information and Disclaimer:The information provided on this page represents TI's knowledge and belief as of the date that it is provided. TI bases its knowledge and belief on information
provided by third parties, and makes no representation or warranty as to the accuracy of such information. Efforts are underway to better integrate information from third parties. TI has taken and
continues to take reasonable steps to provide representative and accurate information but may not have conducted destructive testing or chemical analysis on incoming materials and chemicals.
TI and TI suppliers consider certain information to be proprietary, and thus CAS numbers and other limited information may not be available for release.
In no event shall TI's liability arising out of such information exceed the total purchase price of the TI part(s) at issue in this document sold by TI to Customer on an annual basis.
Addendum-Page 2
PACKAGE MATERIALS INFORMATION
www.ti.com
23-Sep-2013
TAPE AND REEL INFORMATION
*All dimensions are nominal
Device
Package Package Pins
Type Drawing
SPQ
Reel
Reel
A0
B0
K0
P1
W
Pin1
Diameter Width (mm) (mm) (mm) (mm) (mm) Quadrant
(mm) W1 (mm)
LM2651MTCX-3.3/NOPB TSSOP
LM2651MTCX-ADJ/NOPB TSSOP
PW
PW
16
16
2500
2500
330.0
330.0
12.4
12.4
6.95
6.95
8.3
8.3
1.6
1.6
8.0
8.0
12.0
12.0
Q1
Q1
Pack Materials-Page 1
PACKAGE MATERIALS INFORMATION
www.ti.com
23-Sep-2013
*All dimensions are nominal
Device
Package Type Package Drawing Pins
SPQ
Length (mm) Width (mm) Height (mm)
LM2651MTCX-3.3/NOPB
LM2651MTCX-ADJ/NOPB
TSSOP
TSSOP
PW
PW
16
16
2500
2500
367.0
367.0
367.0
367.0
35.0
35.0
Pack Materials-Page 2
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LM2651MTCX-ADJ CAD模型
引脚图
封装焊盘图
LM2651MTCX-ADJ 替代型号
| 型号 | 制造商 | 描述 | 替代类型 | 文档 |
| LM2651MTCX-ADJ/NOPB | TI | 1.5A 高效开关稳压器 | PW | 16 | -40 to 125 | 完全替代 |
|
| LM2651MTC-ADJ/NOPB | TI | 1.5A 高效开关稳压器 | PW | 16 | -40 to 125 | 类似代替 |
|
| LM2651MTC-ADJ | TI | 1.5A 高效开关稳压器 | PW | 16 | -40 to 125 | 类似代替 |
|
LM2651MTCX-ADJ 相关器件
| 型号 | 制造商 | 描述 | 价格 | 文档 |
| LM2651MTCX-ADJ/NOPB | NSC | IC 2.6 A SWITCHING REGULATOR, 345 kHz SWITCHING FREQ-MAX, PDSO16, TSSOP-16, Switching Regulator or Controller | 获取价格 |
|
| LM2651MTCX-ADJ/NOPB | TI | 1.5A 高效开关稳压器 | PW | 16 | -40 to 125 | 获取价格 |
|
| LM2651_05 | NSC | 1.5A High Efficiency Synchronous Switching Regulator | 获取价格 |
|
| LM2652 | NSC | 1.5A, Dual High Performance Synchronous Buck Regulator | 获取价格 |
|
| LM2652MTC | NSC | 1.5A, Dual High Performance Synchronous Buck Regulator | 获取价格 |
|
| LM2653 | NSC | 1.5A High Efficiency Synchronous Switching Regulator | 获取价格 |
|
| LM2653 | TI | 1.5A 高效同步开关稳压器 | 获取价格 |
|
| LM2653MTC-ADJ | NSC | 1.5A High Efficiency Synchronous Switching Regulator | 获取价格 |
|
| LM2653MTC-ADJ | TI | LM2653 1.5A High Efficiency Synchronous Switching Regulator | 获取价格 |
|
| LM2653MTC-ADJ/NOPB | TI | LM2653 1.5A High Efficiency Synchronous Switching Regulator | 获取价格 |
|
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