LM6172AMJ-QMLV [TI]
2 CHANNEL, VIDEO AMPLIFIER, CDIP8, CERDIP-8;
| 型号： | LM6172AMJ-QMLV |
| 厂家： | 
TEXAS INSTRUMENTS |
| 描述： | 2 CHANNEL, VIDEO AMPLIFIER, CDIP8, CERDIP-8 放大器 CD 商用集成电路 |
| 文件： | 总20页 (文件大小：626K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
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Search http://www.ti.com/ for the latest technical
information and details on our current products and services.
September 2004
LM6172
Dual High Speed, Low Power, Low Distortion, Voltage
Feedback Amplifiers
General Description
Features
The LM6172 is a dual high speed voltage feedback amplifier.
It is unity-gain stable and provides excellent DC and AC
performance. With 100MHz unity-gain bandwidth, 3000V/µs
slew rate and 50mA of output current per channel, the
LM6172 offers high performance in dual amplifiers; yet it
only consumes 2.3mA of supply current each channel.
(Typical Unless Otherwise Noted)
n Easy to Use Voltage Feedback Topology
n High Slew Rate 3000V/µs
n Wide Unity-Gain Bandwidth 100MHz
n Low Supply Current 2.3mA/Channel
n High Output Current 50mA/channel
n Specified for 15V and 5V Operation
The LM6172 operates on 15V power supply for systems
requiring large voltage swings, such as ADSL, scanners and
ultrasound equipment. It is also specified at 5V power
supply for low voltage applications such as portable video
systems.
Applications
n Scanner I-to-V Converters
n ADSL/HDSL Drivers
™
The LM6172 is built with National’s advanced VIP III (Ver-
tically Integrated PNP) complementary bipolar process. See
the LM6171 datasheet for a single amplifier with these same
features.
n Multimedia Broadcast Systems
n Video Amplifiers
n NTSC, PAL® and SECAM Systems
n ADC/DAC Buffers
n Pulse Amplifiers and Peak Detectors
LM6172 Driving Capacitive Load
01258144
01258150
Connection Diagram
8-Pin DIP/SO
01258101
Top View
™
VIP is a trademark of National Semiconductor Corporation.
PAL® is a registered trademark of and used under license from Advanced Micro Devices, Inc.
© 2004 National Semiconductor Corporation
DS012581
www.national.com
Ordering Information
Package
Temperature Range
Transport Media
NSC Drawing
Industrial
Military
−40˚C to +85˚C
LM6172IN
−55˚C to +125˚C
8-Pin DIP
8-Pin CDIP
16-Pin Ceramic
SOIC
Rails
Rails
Trays
N08E
J08A
LM6172AMJ-QML
LM6172AMWG-QML
5962-95604
5962-95604
WG16A
8-Pin
LM6172IM
Rails
M08A
Small Outline
LM6172IMX
Tape and Reel
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2
Absolute Maximum Ratings (Note 1)
Soldering Information
Infrared or Convection Reflow
(20 sec.)
If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales Office/
Distributors for availability and specifications.
235˚C
260˚C
Wave Soldering Lead Temp
(10 sec.)
ESD Tolerance (Note 2)
Human Body Model
3kV
Machine Model
300V
Operating Ratings(Note 1)
Supply Voltage
Supply Voltage (V+ − V−)
Differential Input Voltage
Common Mode Voltage Range
Input Current
36V
5.5V ≤ VS ≤ 36V
10V
Operating Temperature Range
LM6172I
V+ +0.3V to V− −0.3V
10mA
−40˚C to +85˚C
Thermal Resistance (θJA
)
Output Short Circuit to Ground
(Note 3)
N Package, 8-Pin Molded DIP
95˚C/W
Continuous
M Package, 8-Pin Surface Mount
160˚C/W
Storage Temp. Range
Maximum Junction Temperature
(Note 4)
−65˚C to +150˚C
150˚C
15V DC Electrical Characteristics
Unless otherwise specified, all limits guaranteed for TJ = 25˚C,V+ = +15V, V− = −15V, VCM = 0V, and RL = 1kΩ. Boldface
limits apply at the temperature extremes
Symbol
Parameter
Conditions
Typ
LM6172I
Units
(Note 5)
Limit
(Note 6)
VOS
TC VOS
IB
Input Offset Voltage
0.4
6
3
mV
4
max
Input Offset Voltage
Average Drift
µV/˚C
Input Bias Current
1.2
0.02
3
4
2
3
µA
max
µA
IOS
Input Offset Current
Input Resistance
max
MΩ
RIN
Common Mode
40
4.9
14
Differential Mode
RO
Open Loop Output Resistance
Common Mode Rejection Ratio
Ω
dB
min
dB
min
V
CMRR
VCM
VS
=
10V
110
70
65
75
70
PSRR
Power Supply Rejection Ratio
=
15V to 5V
95
VCM
AV
Input Common Mode Voltage Range CMRR ≥ 60dB
13.5
86
Large Signal Voltage
Gain (Note 7)
RL = 1kΩ
RL = 100Ω
RL = 1kΩ
80
75
dB
min
dB
min
V
78
13.2
−13.1
9
65
60
VO
Output Swing
12.5
12
min
V
−12.5
−12
6
max
V
RL = 100Ω
5
min
V
−8.5
90
−6
−5
max
mA
min
Continuous Output Current
(Open Loop) (Note 8)
Sourcing, RL = 100Ω
60
50
3
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15V DC Electrical Characteristics (Continued)
Unless otherwise specified, all limits guaranteed for TJ = 25˚C,V+ = +15V, V− = −15V, VCM = 0V, and RL = 1kΩ. Boldface
limits apply at the temperature extremes
Symbol
Parameter
Conditions
Typ
(Note 5)
LM6172I
Limit
Units
(Note 6)
−60
Sinking, RL = 100Ω
−85
mA
max
mA
−50
ISC
IS
Output Short Circuit
Current
Sourcing
107
−105
4.6
Sinking
mA
Supply Current
Both Amplifiers
8
mA
9
max
15V AC Electrical Characteristics
Unless otherwise specified, TJ = 25˚C, V+ = +15V, V− = −15V, VCM = 0V, and RL = 1kΩ
LM6172I
Typ
(Note 5)
3000
2500
100
Symbol
SR
Parameter
Conditions
Units
Slew Rate
AV = +2, VIN = 13 VPP
AV = +2, VIN = 10 VPP
V/µs
V/µs
MHz
MHz
MHz
MHz
Deg
ns
Unity-Gain Bandwidth
−3 dB Frequency
AV = +1
AV = +2
160
62
Bandwidth Matching between Channels
Phase Margin
2
φm
40
ts
Settling Time (0.1%)
AV = −1, VOUT
=
5V,
65
RL = 500Ω
AD
φD
en
Differential Gain (Note 9)
Differential Phase (Note 9)
Input-Referred
0.28
0.6
12
%
Deg
f = 1kHz
f = 1kHz
Voltage Noise
Input-Referred
Current Noise
in
1
Second Harmonic
Distortion (Note 10)
Third Harmonic
f = 10kHz
f = 5MHz
f = 10kHz
f = 5MHz
−110
−50
dB
dB
dB
dB
−105
−50
Distortion (Note 10)
5V DC Electrical Characteristics
Unless otherwise specified, all limits guaranteed for TJ = 25˚C, V+ = +5V, V− = −5V, VCM = 0V, and RL = 1 kΩ. Boldface lim-
its apply at the temperature extremes
Symbol
Parameter
Conditions
Typ
LM6172I
Units
(Note 5)
Limit
(Note 6)
VOS
TC VOS
IB
Input Offset Voltage
0.1
4
3
mV
4
max
Input Offset Voltage
Average Drift
µV/˚C
Input Bias Current
1.4
0.02
2.5
3.5
1.5
µA
max
µA
IOS
Input Offset Current
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4
5V DC Electrical Characteristics (Continued)
Unless otherwise specified, all limits guaranteed for TJ = 25˚C, V+ = +5V, V− = −5V, VCM = 0V, and RL = 1 kΩ. Boldface lim-
its apply at the temperature extremes
Symbol
Parameter
Conditions
Typ
(Note 5)
LM6172I
Limit
Units
(Note 6)
2.2
max
RIN
Input Resistance
Common Mode
40
4.9
14
MΩ
Differential Mode
RO
Output Resistance
Ω
dB
CMRR
Common Mode Rejection Ratio
VCM
VS
=
2.5V
105
70
65
75
70
min
dB
PSRR
Power Supply Rejection Ratio
=
15V to 5V
95
min
V
VCM
AV
Input Common Mode Voltage Range CMRR ≥ 60dB
3.7
82
Large Signal Voltage
Gain (Note 7)
RL = 1kΩ
RL = 100Ω
RL = 1kΩ
70
65
dB
min
dB
78
3.4
65
60
min
V
VO
Output Swing
3.1
3
min
V
−3.3
2.9
−3.1
−3
max
V
RL = 100Ω
2.5
2.4
−2.4
−2.3
25
min
V
−2.7
29
max
mA
min
mA
max
mA
mA
mA
max
Continuous Output Current
(Open Loop) (Note 8)
Sourcing, RL = 100Ω
Sinking, RL = 100Ω
24
−27
−24
−23
ISC
IS
Output Short Circuit
Current
Sourcing
93
−72
4.4
Sinking
Supply Current
Both Amplifiers
6
7
5V AC Electrical Characteristics
Unless otherwise specified, TJ = 25˚C, V+ = +5V, V− = −5V, VCM = 0V, and RL = 1 kΩ.
LM61722
Typ
(Note 5)
Symbol
SR
Parameter
Conditions
Units
Slew Rate
AV = +2, VIN = 3.5 VPP
750
70
V/µs
MHz
MHz
MHz
Deg
ns
Unity-Gain Bandwidth
−3 dB Frequency
AV = +1
AV = +2
130
45
φm
Phase Margin
57
ts
Settling Time (0.1%)
AV = −1, VOUT
=
1V,
72
RL = 500Ω
AD
Differential Gain (Note 9)
Differential Phase (Note 9)
0.4
0.7
%
φD
Deg
5
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5V AC Electrical Characteristics (Continued)
Unless otherwise specified, TJ = 25˚C, V+ = +5V, V− = −5V, VCM = 0V, and RL = 1 kΩ.
LM61722
Typ
(Note 5)
Symbol
Parameter
Input-Referred
Conditions
f = 1kHz
Units
en
11
1
Voltage Noise
Input-Referred
Current Noise
in
f = 1kHz
Second Harmonic
Distortion (Note 10)
Third Harmonic
f = 10kHz
f = 5MHz
f = 10kHz
f = 5MHz
−110
−48
dB
dB
dB
dB
−105
−50
Distortion (Note 10)
Note 1: Absolute Maximum Ratings indicate limits beyond which damage to the device may occur. Operating Ratings indicate conditions for which the device is
intended to be functional, but specific performance is not guaranteed. For guaranteed specifications and the test conditions, see the Electrical Characteristics.
Note 2: Human body model, 1.5kΩ in series with 100pF. Machine Model, 200Ω in series with 100pF.
Note 3: Continuous short circuit operation can result in exceeding the maximum allowed junction temperature of 150˚C.
Note 4: The maximum power dissipation is a function of T
, θ , and T . The maximum allowable power dissipation at any ambient temperature is
A
J(max) JA
P
D
= (T
− T )/θ . All numbers apply for packages soldered directly into a PC board.
J(max) A JA
Note 5: Typical Values represent the most likely parametric norm.
Note 6: All limits are guaranteed by testing or statistical analysis.
Note 7: Large signal voltage gain is the total output swing divided by the input signal required to produce that swing. For V
=
15V, V
=
5V. For V =
S
5V,
S
OUT
V
=
1V.
Note 8: The open loop output current is the output swing with the 100Ω load resistor divided by that resistor.
Note 9: Differential gain and phase are measured with A = +2, V = 1 V at 3.58MHz and both input and output 75Ω terminated.
OUT
V
IN
PP
Note 10: Harmonics are measured with A = +2, V = 1 V and R = 100Ω.
V
IN
PP
L
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6
Typical Performance Characteristics unless otherwise noted, TA = 25˚C
Supply Voltage vs. Supply Current
Supply Current vs. Temperature
01258114
01258115
Input Offset Voltage vs. Temperature
Input Bias Current vs. Temperature
01258116
01258117
Short Circuit Current vs. Temperature (Sourcing)
Short Circuit Current vs. Temperature (Sinking)
01258118
01258135
7
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Typical Performance Characteristics unless otherwise noted, TA = 25˚C (Continued)
Output Voltage vs. Output Current
(VS 15V)
Output Voltage vs. Output Current
(VS 5V)
=
=
01258136
01258137
CMRR vs. Frequency
PSRR vs. Frequency
01258119
01258120
PSRR vs. Frequency
Open-Loop Frequency Response
01258133
01258121
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8
Typical Performance Characteristics unless otherwise noted, TA = 25˚C (Continued)
Gain-Bandwidth Product vs. Supply Voltage at Different
Temperature
Open-Loop Frequency Response
01258123
01258122
Large Signal Voltage Gain vs. Load
Large Signal Voltage Gain vs. Load
01258138
01258139
Input Voltage Noise vs. Frequency
Input Voltage Noise vs. Frequency
01258140
01258141
9
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Typical Performance Characteristics unless otherwise noted, TA = 25˚C (Continued)
Input Current Noise vs. Frequency
Input Current Noise vs. Frequency
01258142
01258143
Slew Rate vs. Supply Voltage
Slew Rate vs. Input Voltage
01258125
01258126
Large Signal Pulse Response
AV = +1, VS 15V
Small Signal Pulse Response
AV = +1, VS 15V
=
=
01258102
01258103
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10
Typical Performance Characteristics unless otherwise noted, TA = 25˚C (Continued)
Large Signal Pulse Response
AV = +1, VS 5V
Small Signal Pulse Response
AV = +1, VS 5V
=
=
01258104
01258105
Large Signal Pulse Response
AV = +2, VS 15V
Small Signal Pulse Response
AV = +2, VS 15V
=
=
01258106
01258107
Large Signal Pulse Response
AV = +2, VS 5V
Small Signal Pulse Response
AV = +2, VS 5V
=
=
01258108
01258109
11
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Typical Performance Characteristics unless otherwise noted, TA = 25˚C (Continued)
Large Signal Pulse Response
AV = −1, VS 15V
Small Signal Pulse Response
AV = −1, VS 15V
=
=
01258110
01258111
Large Signal Pulse Response
AV = −1, VS 5V
Small Signal Pulse Response
AV = −1, VS 5V
=
=
01258112
01258113
Closed Loop Frequency Response vs. Supply Voltage
(AV = +1)
Closed Loop Frequency Response vs. Supply Voltage
(AV = +2)
01258128
01258129
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Typical Performance Characteristics unless otherwise noted, TA = 25˚C (Continued)
Harmonic Distortion vs. Frequency
(VS 15V)
Harmonic Distortion vs. Frequency
(VS 5V)
=
=
01258130
01258134
Crosstalk Rejection vs. Frequency
Maximum Power Dissipation vs. Ambient Temperature
01258132
01258131
13
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LM6172 Simplified Schematic (Each Amplifier)
01258155
Application Notes
LM6172 PERFORMANCE DISCUSSION
The LM6172 is a dual high-speed, low power, voltage feed-
back amplifier. It is unity-gain stable and offers outstanding
performance with only 2.3mA of supply current per channel.
The combination of 100MHz unity-gain bandwidth, 3000V/µs
slew rate, 50mA per channel output current and other attrac-
tive features makes it easy to implement the LM6172 in
various applications. Quiescent power of the LM6172 is
138mW operating at 15V supply and 46mW at 5V supply.
decrease slew rate. A feedback capacitor can also be used
to reduce overshoot and undershoot. This feedback capaci-
tor serves as a zero to increase the stability of the amplifier
circuit. A 2pF feedback capacitor is recommended for initial
evaluation. When the LM6172 is configured as a buffer, a
feedback resistor of 1kΩ must be added in parallel to the
feedback capacitor.
Another possible source of overshoot and undershoot
comes from capacitive load at the output. Please see the
section “Driving Capacitive Loads” for more detail.
LM6172 CIRCUIT OPERATION
The class AB input stage in LM6172 is fully symmetrical and
has a similar slewing characteristic to the current feedback
amplifiers. In the LM6172 Simplified Schematic, Q1 through
Q4 form the equivalent of the current feedback input buffer,
RE the equivalent of the feedback resistor, and stage A
buffers the inverting input. The triple-buffered output stage
isolates the gain stage from the load to provide low output
impedance.
DRIVING CAPACITIVE LOADS
Amplifiers driving capacitive loads can oscillate or have ring-
ing at the output. To eliminate oscillation or reduce ringing,
an isolation resistor can be placed as shown in Figure 1. The
combination of the isolation resistor and the load capacitor
forms a pole to increase stability by adding more phase
margin to the overall system. The desired performance de-
pends on the value of the isolation resistor; the bigger the
isolation resistor, the more damped (slow) the pulse re-
sponse becomes. For LM6172, a 50Ω isolation resistor is
recommended for initial evaluation.
LM6172 SLEW RATE CHARACTERISTIC
The slew rate of LM6172 is determined by the current avail-
able to charge and discharge an internal high impedance
node capacitor. This current is the differential input voltage
divided by the total degeneration resistor RE. Therefore, the
slew rate is proportional to the input voltage level, and the
higher slew rates are achievable in the lower gain configu-
rations.
When a very fast large signal pulse is applied to the input of
an amplifier, some overshoot or undershoot occurs. By plac-
ing an external series resistor such as 1kΩ to the input of
LM6172, the slew rate is reduced to help lower the over-
shoot, which reduces settling time.
01258145
REDUCING SETTLING TIME
The LM6172 has a very fast slew rate that causes overshoot
and undershoot. To reduce settling time on LM6172, a 1kΩ
resistor can be placed in series with the input signal to
FIGURE 1. Isolation Resistor Used
to Drive Capacitive Load
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14
LAYOUT CONSIDERATION
Application Notes (Continued)
PRINTED CIRCUIT BOARDS AND HIGH SPEED OP
AMPS
There are many things to consider when designing PC
boards for high speed op amps. Without proper caution, it is
very easy to have excessive ringing, oscillation and other
degraded AC performance in high speed circuits. As a rule,
the signal traces should be short and wide to provide low
inductance and low impedance paths. Any unused board
space needs to be grounded to reduce stray signal pickup.
Critical components should also be grounded at a common
point to eliminate voltage drop. Sockets add capacitance to
the board and can affect frequency performance. It is better
to solder the amplifier directly into the PC board without
using any socket.
01258151
USING PROBES
Active (FET) probes are ideal for taking high frequency
measurements because they have wide bandwidth, high
input impedance and low input capacitance. However, the
probe ground leads provide a long ground loop that will
produce errors in measurement. Instead, the probes can be
grounded directly by removing the ground leads and probe
jackets and using scope probe jacks.
FIGURE 2. The LM6172 Driving a 510pF Load
with a 30Ω Isolation Resistor
COMPONENTS SELECTION AND FEEDBACK
RESISTOR
It is important in high speed applications to keep all compo-
nent leads short because wires are inductive at high fre-
quency. For discrete components, choose carbon
composition-type resistors and mica-type capacitors. Sur-
face mount components are preferred over discrete compo-
nents for minimum inductive effect.
Large values of feedback resistors can couple with parasitic
capacitance and cause undesirable effects such as ringing
or oscillation in high speed amplifiers. For LM6172, a feed-
back resistor less than 1kΩ gives optimal performance.
01258152
FIGURE 3. The LM6172 Driving a 220 pF Load
with a 50Ω Isolation Resistor
COMPENSATION FOR INPUT CAPACITANCE
The combination of an amplifier’s input capacitance with the
gain setting resistors adds a pole that can cause peaking or
oscillation. To solve this problem, a feedback capacitor with
a value
>
CF (RG x CIN)/RF
can be used to cancel that pole. For LM6172, a feedback
capacitor of 2pF is recommended. Figure 4 illustrates the
compensation circuit.
01258146
FIGURE 4. Compensating for Input Capacitance
15
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Application Notes (Continued)
POWER SUPPLY BYPASSING
Bypassing the power supply is necessary to maintain low
power supply impedance across frequency. Both positive
and negative power supplies should be bypassed individu-
ally by placing 0.01µF ceramic capacitors directly to power
supply pins and 2.2µF tantalum capacitors close to the
power supply pins.
01258154
FIGURE 7. Improperly Terminated Signal
To minimize reflection, coaxial cable with matching charac-
teristic impedance to the signal source should be used. The
other end of the cable should be terminated with the same
value terminator or resistor. For the commonly used cables,
RG59 has 75Ω characteristic impedance, and RG58 has
50Ω characteristic impedance.
01258147
FIGURE 5. Power Supply Bypassing
POWER DISSIPATION
The maximum power allowed to dissipate in a device is
defined as:
TERMINATION
PD = (TJ(max) − TA)/θJA
Where PD is the power dissipation in a device
TJ(max) is the maximum junction temperature
TA is the ambient temperature
In high frequency applications, reflections occur if signals
are not properly terminated. Figure 6 shows a properly ter-
minated signal while Figure 7 shows an improperly termi-
nated signal.
θJA is the thermal resistance of a particular package
For example, for the LM6172 in a SO-8 package, the maxi-
mum power dissipation at 25˚C ambient temperature is
780mW.
Thermal resistance, θJA, depends on parameters such as
die size, package size and package material. The smaller
the die size and package, the higher θJA becomes. The 8-pin
DIP package has a lower thermal resistance (95˚C/W) than
that of 8-pin SO (160˚C/W). Therefore, for higher dissipation
capability, use an 8-pin DIP package.
The total power dissipated in a device can be calculated as:
PD = PQ + PL
PQ is the quiescent power dissipated in a device with no load
connected at the output. PL is the power dissipated in the
device with a load connected at the output; it is not the power
dissipated by the load.
01258153
FIGURE 6. Properly Terminated Signal
Furthermore,
PQ: = supply current x total supply voltage with no load
PL:
=
output current x (voltage difference between supply
voltage and output voltage of the same supply)
For example, the total power dissipated by the LM6172 with
VS 15V and both channels swinging output voltage of
=
10V into 1kΩ is
PD: = PQ + PL
:
:
:
=
=
=
2[(2.3mA)(30V)] + 2[(10mA)(15V − 10V)]
138mW + 100mW
238mW
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Application Circuits
I-to-V Converters
01258148
Differential Line Driver
01258149
17
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Physical Dimensions inches (millimeters) unless otherwise noted
8-Lead Ceramic Dual-In-Line Package
Order Number LM6172AMJ-QML or 5962-9560401QPA
NS Package Number J08A
8-Lead (0.150" Wide) Molded Small Outline Package, JEDEC
Order Number LM6172IM or LM6172IMX
NS Package Number M08A
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18
Physical Dimensions inches (millimeters) unless otherwise noted (Continued)
8-Lead (0.300" Wide) Molded Dual-In-Line Package
Order Number LM6172IN
NS Package Number N08E
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the right at any time without notice to change said circuitry and specifications.
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