LMP2014MT [TI]
四路、高精度、轨到轨输出运算放大器;
| 型号： | LMP2014MT |
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TEXAS INSTRUMENTS |
| 描述： | 四路、高精度、轨到轨输出运算放大器 放大器 光电二极管 运算放大器 |
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LMP2014MT
www.ti.com
SNOSAK6B –DECEMBER 2004–REVISED MARCH 2013
LMP2014MT Quad High Precision, Rail-to-Rail Output Operational Amplifier
Check for Samples: LMP2014MT
1
FEATURES
DESCRIPTION
The LMP2014MT is a member of Texas Instruments'
new LMPTM precision amplifier family. The
LMP2014MT offers unprecedented accuracy and
stability while also being offered at an affordable
price. This device utilizes patented techniques to
measure and continually correct the input offset error
voltage. The result is an amplifier which is ultra stable
over time and temperature. It has excellent CMRR
and PSRR ratings, and does not exhibit the familiar
1/f voltage and current noise increase that plagues
traditional amplifiers. The combination of the
LMP2014 characteristics makes it a good choice for
transducer amplifiers, high gain configurations, ADC
buffer amplifiers, DAC I-V conversion, and any other
2.7V-5V application requiring precision and long term
stability.
2
•
(For VS = 5V, Typical Unless Otherwise Noted)
Low Specified VOS Over Temperature 60 µV
Low Noise with No 1/f 35nV/√Hz
High CMRR 130 dB
•
•
•
•
•
•
•
•
•
•
High PSRR 120 dB
High AVOL 130 dB
Wide Gain-Bandwidth Product 3 MHz
High Slew Rate 4 V/µs
Low Supply Current 3.7 mA
Rail-to-Rail Output 30 mV
No External Capacitors Required
APPLICATIONS
Other useful benefits of the LMP2014 are rail-to-rail
output, a low supply current of 3.7 mA, and wide
gain-bandwidth product of 3 MHz. These extremely
versatile features found in the LMP2014 provide high
performance and ease of use.
•
•
•
Precision Instrumentation Amplifiers
Thermocouple Amplifiers
Strain Gauge Bridge Amplifier
Connection Diagram
Figure 1. 14-Pin TSSOP – Top View
See Package Number PW
1
Please be aware that an important notice concerning availability, standard warranty, and use in critical applications of
Texas Instruments semiconductor products and disclaimers thereto appears at the end of this data sheet.
All trademarks are the property of their respective owners.
2
PRODUCTION DATA information is current as of publication date.
Products conform to specifications per the terms of the Texas
Instruments standard warranty. Production processing does not
necessarily include testing of all parameters.
Copyright © 2004–2013, Texas Instruments Incorporated
LMP2014MT
SNOSAK6B –DECEMBER 2004–REVISED MARCH 2013
www.ti.com
These devices have limited built-in ESD protection. The leads should be shorted together or the device placed in conductive foam
during storage or handling to prevent electrostatic damage to the MOS gates.
Absolute Maximum Ratings(1)(2)
ESD Tolerance
Human Body Model
Machine Model
2000V
200V
5.8V
Supply Voltage
Common-Mode Input Voltage
Lead Temperature (soldering 10 sec.)
Differential Input Voltage
Current at Input Pin
−0.3 ≤ VCM ≤ VCC +0.3V
+300°C
±Supply Voltage
30 mA
Current at Output Pin
30 mA
Current at Power Supply Pin
50 mA
(1) Absolute Maximum Ratings indicate limits beyond which damage may occur. Operating Ratings indicate conditions for which the device
is intended to be functional, but specific performance is not ensured. For ensured specifications and test conditions, see the Electrical
Characteristics.
(2) If Military/Aerospace specified devices are required, please contact the TI Sales Office/ Distributors for availability and specifications.
Operating Ratings(1)
Supply Voltage
2.7V to 5.25V
−65°C to 150°C
0°C to 70°C
Storage Temperature Range
Operating Temperature Range
LMP2014MT, LMP2014MTX
(1) Absolute Maximum Ratings indicate limits beyond which damage may occur. Operating Ratings indicate conditions for which the device
is intended to be functional, but specific performance is not ensured. For ensured specifications and test conditions, see the Electrical
Characteristics.
2.7V DC Electrical Characteristics
Unless otherwise specified, all limits specified for T J = 25°C, V+ = 2.7V, V-= 0V, V CM = 1.35V, VO = 1.35V and RL > 1 MΩ.
Boldface limits apply at the temperature extremes.
Symbol
VOS
Parameter
Conditions
Min(1)
Typ(2)
Max(1)
Units
Input Offset Voltage
0.8
30
μV
60
Offset Calibration Time
0.5
10
ms
12
TCVOS
Input Offset Voltage
Long-Term Offset Drift
Lifetime VOS Drift
0.015
0.006
2.5
-3
μV/°C
μV/month
μV
IIN
Input Current
pA
IOS
Input Offset Current
Input Differential Resistance
Common Mode Rejection Ratio
6
pA
RIND
CMRR
9
MΩ
−0.3 ≤ VCM ≤ 0.9V
95
130
dB
0 ≤ VCM ≤ 0.9V
90
PSRR
AVOL
Power Supply Rejection Ratio
Open Loop Voltage Gain
95
90
120
130
124
dB
dB
RL = 10 kΩ
RL = 2 kΩ
95
90
90
85
(1) Limits are 100% production tested at 25°C. Limits over the operating temperature range are specified through correlations using
statistical quality control (SQC) method.
(2) Typical values represent the most likely parametric norm.
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SNOSAK6B –DECEMBER 2004–REVISED MARCH 2013
2.7V DC Electrical Characteristics (continued)
Unless otherwise specified, all limits specified for T J = 25°C, V+ = 2.7V, V-= 0V, V CM = 1.35V, VO = 1.35V and RL > 1 MΩ.
Boldface limits apply at the temperature extremes.
Symbol
VO
Parameter
Output Swing
Conditions
Min(1)
Typ(2)
Max(1)
Units
RL = 10 kΩ to 1.35V
2.63
2.68
VIN(diff) = ±0.5V
2.655
V
0.033
2.65
0.061
12
0.070
0.075
RL = 2 kΩ to 1.35V
VIN(diff) = ±0.5V
2.615
2.615
V
0.085
0.105
IO
Output Current
Sourcing, VO = 0V
VIN(diff) = ±0.5V
5
3
mA
mA
Sinking, VO = 5V
VIN(diff) = ±0.5V
5
3
18
IS
Supply Current per Channel
0.919
1.20
1.50
2.7V AC Electrical Characteristics
TJ = 25°C, V+ = 2.7V, V -= 0V, VCM = 1.35V, VO = 1.35V, and RL > 1 MΩ. Boldface limits apply at the temperature extremes.
(1)
Symbol
GBW
Parameter
Gain-Bandwidth Product
Slew Rate
Conditions
Min(1)
Typ(2)
Max
Units
MHz
V/μs
3
SR
θ m
Gm
en
4
Phase Margin
60
Deg
Gain Margin
−14
35
dB
Input-Referred Voltage Noise
Input-Referred Current Noise
Input-Referred Voltage Noise
Input Overload Recovery Time
nV/√Hz
pA/√Hz
nVpp
ms
in
enp-p
trec
RS = 100Ω, DC to 10 Hz
850
50
(1) Limits are 100% production tested at 25°C. Limits over the operating temperature range are specified through correlations using
statistical quality control (SQC) method.
(2) Typical values represent the most likely parametric norm.
5V DC Electrical Characteristics
Unless otherwise specified, all limits specified for T J = 25°C, V+ = 5V, V-= 0V, V CM = 2.5V, VO = 2.5V and RL > 1MΩ.
Boldface limits apply at the temperature extremes.
Symbol
VOS
Parameter
Conditions
Min(1)
Typ(2)
Max(1)
Units
Input Offset Voltage
0.12
30
μV
60
Offset Calibration Time
0.5
10
ms
12
TCVOS
Input Offset Voltage
Long-Term Offset Drift
Lifetime VOS Drift
0.015
0.006
2.5
-3
μV/°C
μV/month
μV
IIN
Input Current
pA
IOS
Input Offset Current
Input Differential Resistance
Common Mode Rejection Ratio
6
pA
RIND
CMRR
9
MΩ
−0.3 ≤ VCM ≤ 3.2
0 ≤ VCM ≤ 3.2
100
90
130
dB
(1) Limits are 100% production tested at 25°C. Limits over the operating temperature range are specified through correlations using
statistical quality control (SQC) method.
(2) Typical values represent the most likely parametric norm.
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5V DC Electrical Characteristics (continued)
Unless otherwise specified, all limits specified for T J = 25°C, V+ = 5V, V-= 0V, V CM = 2.5V, VO = 2.5V and RL > 1MΩ.
Boldface limits apply at the temperature extremes.
Symbol
Parameter
Conditions
Min(1)
Typ(2)
Max(1)
Units
PSRR
Power Supply Rejection Ratio
95
120
dB
90
AVOL
Open Loop Voltage Gain
Output Swing
RL = 10 kΩ
RL = 2 kΩ
105
100
130
132
dB
V
95
90
VO
RL = 10 kΩ to 2.5V
VIN(diff) = ±0.5V
4.92
4.95
4.978
0.040
4.919
0.091
15
0.080
0.085
RL = 2 kΩ to 2.5V
VIN(diff) = ±0.5V
4.875
4.875
V
0.125
0.140
IO
Output Current
Sourcing, VO = 0V
VIN(diff) = ±0.5V
8
6
mA
mA
Sinking, VO = 5V
V IN(diff) = ±0.5V
8
6
17
IS
Supply Current per Channel
0.930
1.20
1.50
5V AC Electrical Characteristics
TJ = 25°C, V+ = 5V, V -= 0V, VCM = 2.5V, VO = 2.5V, and RL > 1MΩ. Boldface limits apply at the temperature extremes.
Symbol
GBW
Parameter
Gain-Bandwidth Product
Slew Rate
Conditions
Min(1)
Typ(2)
Max(1)
Units
MHz
V/μs
3
SR
θ m
Gm
en
4
Phase Margin
60
deg
Gain Margin
−15
35
dB
Input-Referred Voltage Noise
Input-Referred Current Noise
Input-Referred Voltage Noise
Input Overload Recovery Time
nV/√Hz
pA/√Hz
nVPP
ms
in
enp-p
trec
RS = 100Ω, DC to 10 Hz
850
50
(1) Limits are 100% production tested at 25°C. Limits over the operating temperature range are specified through correlations using
statistical quality control (SQC) method.
(2) Typical values represent the most likely parametric norm.
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SNOSAK6B –DECEMBER 2004–REVISED MARCH 2013
Typical Performance Characteristics
TA=25C, VS= 5V unless otherwise specified.
Supply Current vs. Supply Voltage
Offset Voltage vs. Supply Voltage
Figure 2.
Figure 3.
Offset Voltage vs. Common Mode
Offset Voltage vs. Common Mode
Figure 4.
Figure 5.
Voltage Noise vs. Frequency
Input Bias Current vs. Common Mode
500
400
300
200
100
0
10000
1000
100
V
= 5V
V = 5V
S
S
-100
-200
-300
-400
-500
10
0.0 0.5 1.0 1.5 2.0 2.5 3.0 3.5 4.0 4.5 5.0
(V)
0.1
1M
1k
10k 100k
1
10
100
V
CM
FREQUENCY (Hz)
Figure 6.
Figure 7.
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Typical Performance Characteristics (continued)
TA=25C, VS= 5V unless otherwise specified.
PSRR vs. Frequency
PSRR vs. Frequency
120
120
100
80
V
V
= 2.7V
V
= 5V
S
S
= 1V
V = 2.5V
CM
CM
100
80
NEGATIVE
NEGATIVE
60
60
40
40
POSITIVE
POSITIVE
20
0
20
0
10
100
1k
10k 100k
1M
10M
10
100
1k
10k 100k
1M
10M
FREQUENCY (Hz)
FREQUENCY (Hz)
Figure 8.
Figure 9.
Output Sourcing @ 2.7V
Output Sourcing @ 5V
Figure 10.
Figure 11.
Output Sinking @ 2.7V
Output Sinking @ 5V
Figure 12.
Figure 13.
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SNOSAK6B –DECEMBER 2004–REVISED MARCH 2013
Typical Performance Characteristics (continued)
TA=25C, VS= 5V unless otherwise specified.
Max Output Swing vs. Supply Voltage
Max Output Swing vs. Supply Voltage
Figure 14.
Figure 15.
Min Output Swing vs. Supply Voltage
Min Output Swing vs. Supply Voltage
Figure 16.
Figure 17.
CMRR vs. Frequency
Open Loop Gain and Phase vs. Supply Voltage
100
150.0
140
V
S
= 5V
V
= 5V
S
120
100
80
120.0
PHASE
V
= 5V
S
60
40
20
0
90.0
60.0
80
60
40
20
0
GAIN
30.0
0.0
R
C
= 1M
L
L
V
= 2.7V
S
= < 20pF
= 2.7V OR 5V
V
S
-30.0
10M
-20
100k
1M
100
1k
10k
10
100
1k
100k
100k
FREQUENCY (Hz)
FREQUENCY (Hz)
Figure 18.
Figure 19.
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Typical Performance Characteristics (continued)
TA=25C, VS= 5V unless otherwise specified.
Open Loop Gain and Phase vs. RL @ 2.7V
Open Loop Gain and Phase vs. RL @ 5V
100
80
100
80
150.0
150.0
R
= >1M
L
120.0
120.0
PHASE
PHASE
R
L
= 2k
60
40
20
0
60
40
20
0
90.0
60.0
90.0
60.0
R
= >1M
L
GAIN
R
= >1M
L
R
= >1M
L
GAIN
30.0
0.0
30.0
0.0
V
= 5V
V
= 2.7V
S
S
R
= 2k
L
C
= < 20 pF
= >1M & 2k
C
= < 20 pF
L
L
L
L
R
L
= 2k
R
R
= >1M & 2k
-30.0
-30.0
-20
-20
100k
FREQUENCY (Hz)
Figure 20.
100k
100
1k
10k
1M
10M
100
1k
10k
1M
10M
FREQUENCY (Hz)
Figure 21.
Open Loop Gain and Phase vs. CL @ 2.7V
Open Loop Gain and Phase vs. CL @ 5V
100
80
150.0
100
150.0
20 pF
20 pF
120.0
80
60
40
20
0
120.0
PHASE
PHASE
20 pF
60
40
20
0
90.0
90.0
20 pF
500 pF
60.0
500 pF
60.0
30.0
0.0
GAIN
GAIN
30.0
0.0
V
= 2.7V, R = >1M
L
S
V
= 5V, R = >1M
L
S
500 pF
C
= 20,50,200 & 500 pF
L
500 pF
1M
C
= 20,50,200 & 500 pF
L
-30.0
10M
-20
-20
-30.0
100
10M
100k
1k
10k
1M
100
1k
10k
100k
FREQUENCY (Hz)
FREQUENCY (Hz)
Figure 22.
Figure 23.
Open Loop Gain and Phase vs. Temperature @ 2.7V
Open Loop Gain and Phase vs. Temperature @ 5V
113
90
68
45
23
0
113
90
68
45
23
0
100
80
60
40
20
0
100
80
60
40
20
0
PHASE
PHASE
0°C
0°C
0°C
0°C
GAIN
GAIN
25°C
25°C
70°C
70°C
70°C
70°C
V
V
= 2.7V
V
V
= 5V
S
S
= 200mV
= 200mV
PP
OUT
PP
OUT
R
= >1M
R
= >1M
L
L
L
L
C
= <20pF
C
= <20pF
-23
-23
-20
-20
1k
10k
100k
1M
10M
1k
10k
100k
1M
10M
FREQUENCY (Hz)
FREQUENCY (Hz)
Figure 24.
Figure 25.
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SNOSAK6B –DECEMBER 2004–REVISED MARCH 2013
Typical Performance Characteristics (continued)
TA=25C, VS= 5V unless otherwise specified.
THD+N vs. AMPL
THD+N vs. Frequency
10
10
MEAS FREQ = 1 KHz
V
= 2 V
PP
OUT
MEAS BW = 500 kHz
MEAS BW = 22 KHz
R
= 10k
= +10
L
R
= 10k
= +10
L
A
V
A
V
1
0.1
V = 2.7V
S
1
V
S
= 2.7V
V
= 5V
S
0.1
0.01
V
S
= 5V
V
S
= 5V
V
= 2.7V
100
S
0.01
0.1
1
10
10
1k
10k
100k
OUTPUT VOLTAGE (V
)
PP
FREQUENCY (Hz)
Figure 26.
Figure 27.
0.1 Hz − 10 Hz Noise vs. Time
1 sec/DIV
Figure 28.
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APPLICATION INFORMATION
THE BENEFITS OF LMP2014 NO 1/f NOISE
Using patented methods, the LMP2014 eliminates the 1/f noise present in other amplifiers. That noise, which
increases as frequency decreases, is a major source of measurement error in all DC-coupled measurements.
Low-frequency noise appears as a constantly-changing signal in series with any measurement being made. As a
result, even when the measurement is made rapidly, this constantly-changing noise signal will corrupt the result.
The value of this noise signal can be surprisingly large. For example: If a conventional amplifier has a flat-band
noise level of 10nV/√Hz and a noise corner of 10 Hz, the RMS noise at 0.001 Hz is 1µV/√Hz. This is equivalent
to a 0.50 µV peak-to-peak error, in the frequency range 0.001 Hz to 1.0 Hz. In a circuit with a gain of 1000, this
produces a 0.50 mV peak-to-peak output error. This number of 0.001 Hz might appear unreasonably low, but
when a data acquisition system is operating for 17 minutes, it has been on long enough to include this error. In
this same time, the LMP2014 will only have a 0.21 mV output error. This is smaller by 2.4 x. Keep in mind that
this 1/f error gets even larger at lower frequencies. At the extreme, many people try to reduce this error by
integrating or taking several samples of the same signal. This is also doomed to failure because the 1/f nature of
this noise means that taking longer samples just moves the measurement into lower frequencies where the noise
level is even higher.
The LMP2014 eliminates this source of error. The noise level is constant with frequency so that reducing the
bandwidth reduces the errors caused by noise.
Another source of error that is rarely mentioned is the error voltage caused by the inadvertent thermocouples
created when the common "Kovar type" IC package lead materials are soldered to a copper printed circuit board.
These steel-based leadframe materials can produce over 35 μV/°C when soldered onto a copper trace. This can
result in thermocouple noise that is equal to the LMP2014 noise when there is a temperature difference of only
0.0014°C between the lead and the board!
For this reason, the lead-frame of the LMP2014 is made of copper. This results in equal and opposite junctions
which cancel this effect.
OVERLOAD RECOVERY
The LMP2014 recovers from input overload much faster than most chopper-stabilized op amps. Recovery from
driving the amplifier to 2X the full scale output, only requires about 40 ms. Many chopper-stabilized amplifiers will
take from 250 ms to several seconds to recover from this same overload. This is because large capacitors are
used to store the unadjusted offset voltage.
Figure 29.
The wide bandwidth of the LMP2014 enhances performance when it is used as an amplifier to drive loads that
inject transients back into the output. ADCs (Analog-to-Digital Converters) and multiplexers are examples of this
type of load. To simulate this type of load, a pulse generator producing a 1V peak square wave was connected
to the output through a 10 pF capacitor. (Figure 29) The typical time for the output to recover to 1% of the
applied pulse is 80 ns. To recover to 0.1% requires 860ns. This rapid recovery is due to the wide bandwidth of
the output stage and large total GBW.
NO EXTERNAL CAPACITORS REQUIRED
The LMP2014 does not need external capacitors. This eliminates the problems caused by capacitor leakage and
dielectric absorption, which can cause delays of several seconds from turn-on until the amplifier's error has
settled.
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SNOSAK6B –DECEMBER 2004–REVISED MARCH 2013
MORE BENEFITS
The LMP2014 offers the benefits mentioned above and more. It has a rail-to-rail output and consumes only 950
µA of supply current while providing excellent DC and AC electrical performance. In DC performance, the
LMP2014 achieves 130 dB of CMRR, 120 dB of PSRR and 130 dB of open loop gain. In AC performance, the
LMP2014 provides 3 MHz of gain-bandwidth product and 4 V/µs of slew rate.
HOW THE LMP2014 WORKS
The LMP2014 uses new, patented techniques to achieve the high DC accuracy traditionally associated with
chopper-stabilized amplifiers without the major drawbacks produced by chopping. The LMP2014 continuously
monitors the input offset and corrects this error. The conventional chopping process produces many mixing
products, both sums and differences, between the chopping frequency and the incoming signal frequency. This
mixing causes large amounts of distortion, particularly when the signal frequency approaches the chopping
frequency. Even without an incoming signal, the chopper harmonics mix with each other to produce even more
trash. If this sounds unlikely or difficult to understand, look at the plot (Figure 30), of the output of a typical
(MAX432) chopper-stabilized op amp. This is the output when there is no incoming signal, just the amplifier in a
gain of -10 with the input grounded. The chopper is operating at about 150 Hz; the rest is mixing products. Add
an input signal and the noise gets much worse. Compare this plot with Figure 31 of the LMP2014. This data was
taken under the exact same conditions. The auto-zero action is visible at about 30 kHz but note the absence of
mixing products at other frequencies. As a result, the LMP2014 has very low distortion of 0.02% and very low
mixing products.
Figure 30.
10000
V
= 5V
S
1000
100
10
0.1
1M
1k
10k 100k
1
10
100
FREQUENCY (Hz)
Figure 31.
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INPUT CURRENTS
The LMP2014's input currents are different than standard bipolar or CMOS input currents in that it appears as a
current flowing in one input and out the other. Under most operating conditions, these currents are in the
picoamp level and will have little or no effect in most circuits. These currents tend to increase slightly when the
common-mode voltage is near the minus supply. (See the typical curves.) At high temperatures such as 70°C,
the input currents become larger, 0.5 nA typical, and are both positive except when the VCM is near V−. If
operation is expected at low common-mode voltages and high temperature, do not add resistance in series with
the inputs to balance the impedances. Doing this can cause an increase in offset voltage. A small resistance
such as 1 kΩ can provide some protection against very large transients or overloads, and will not increase the
offset significantly.
PRECISION STRAIN-GAUGE AMPLIFIER
This Strain-Gauge amplifier (Figure 32) provides high gain (1006 or ~60 dB) with very low offset and drift. Using
the resistors' tolerances as shown, the worst case CMRR will be greater than 108 dB. The CMRR is directly
related to the resistor mismatch. The rejection of common-mode error, at the output, is independent of the
differential gain, which is set by R3. The CMRR is further improved, if the resistor ratio matching is improved, by
specifying tighter-tolerance resistors, or by trimming.
5V
+
V
OUT
-
+
-
R1
R2
2k, 1%
R2
R1
10k, 0.1%
10k, 0.1%
2k, 1%
R3
20W
Figure 32.
Extending Supply Voltages and Output Swing by Using a Composite Amplifier Configuration:
In cases where substantially higher output swing is required with higher supply voltages, arrangements like the
ones shown in Figure 33 and Figure 34 could be used. These configurations utilize the excellent DC performance
of the LMP2014 while at the same time allow the superior voltage and frequency capabilities of the LM6171 to
set the dynamic performance of the overall amplifier. For example, it is possible to achieve ±12V output swing
with 300 MHz of overall GBW (AV = 100) while keeping the worst case output shift due to VOS less than 4 mV.
The LMP2014 output voltage is kept at about mid-point of its overall supply voltage, and its input common mode
voltage range allows the V- terminal to be grounded in one case (Figure 33, inverting operation) and tied to a
small non-critical negative bias in another (Figure 34, non-inverting operation). Higher closed-loop gains are also
possible with a corresponding reduction in realizable bandwidth. Table 1 shows some other closed loop gain
possibilities along with the measured performance in each case.
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C2
R2
R7, 3.9k
+15V
C4
1N4733A
(5.1V)
D1
0.01
mF
R1
2
3
7
-
3
2
Input
7
LMP201X
U1
+
Output
6
6
LM6171
U2
+
4
-
4
-15V
(+2.5V)
+15V R3
20k
R5, 1M
C3
0.01 mF
R4
3.9k
Figure 33.
Table 1. Composite Amplifier Measured Performance
AV
R1
Ω
R2
Ω
C2
pF
BW
MHz
SR
(V/μs)
en p-p
(mVPP
)
50
100
100
500
1000
200
100
1k
10k
10k
8
3.3
2.5
178
174
170
96
37
10
70
100k
100k
100k
0.67
1.75
2.2
3.1
70
200
100
1.4
250
400
0.98
64
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In terms of the measured output peak-to-peak noise, the following relationship holds between output noise
voltage, en p-p, for different closed-loop gain, AV, settings, where −3 dB Bandwidth is BW:
C2
R2
R7, 3.9k
+15V
1N4731A
(4.3V)
D1
C4
0.01
mF
R1
2
3
7
-
3
7
LMP201X
U1
+
Output
6
6
LM6171
U2
+
4
-15V
Input
2
-
4
R6
(-0.7V)
10k
+15V
(+2.5V)
R5, 1M
R3
C5
0.01 mF
20k
C3
0.01 mF
D2
1N4148
R4
3.9k
Figure 34.
It should be kept in mind that in order to minimize the output noise voltage for a given closed-loop gain setting,
one could minimize the overall bandwidth. As can be seen from Equation 1 above, the output noise has a
square-root relationship to the Bandwidth.
In the case of the inverting configuration, it is also possible to increase the input impedance of the overall
amplifier, by raising the value of R1, without having to increase the feed-back resistor, R2, to impractical values,
by utilizing a "Tee" network as feedback. See the LMC6442 Data Sheet (Application Notes section) for more
details on this.
+5V
430W
(0V to 5V Range)
+Input
+5V
+V
REF
+2.5V
-
ADC1203X
LMP201X
+
-V
REF
LM9140-2.5
-Input
V
IN
GND
1M
Figure 35.
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SNOSAK6B –DECEMBER 2004–REVISED MARCH 2013
LMP2014 AS ADC INPUT AMPLIFIER
The LMP2014 is a great choice for an amplifier stage immediately before the input of an ADC (Analog-to-Digital
Converter), whether AC or DC coupled. See Figure 35 and Figure 36. This is because of the following important
characteristics:
a. Very low offset voltage and offset voltage drift over time and temperature allow a high closed-loop gain
setting without introducing any short-term or long-term errors. For example, when set to a closed-loop gain of
100 as the analog input amplifier for a 12-bit A/D converter, the overall conversion error over full operation
temperature and 30 years life of the part (operating at 50°C) would be less than 5 LSBs.
b. Fast large-signal settling time to 0.01% of final value (1.4 μs) allows 12 bit accuracy at 100 KHZ or more
sampling rate.
c. No flicker (1/f) noise means unsurpassed data accuracy over any measurement period of time, no matter
how long. Consider the following op amp performance, based on a typical low-noise, high-performance
commercially-available device, for comparison:
Op amp flatband noise = 8nV/√Hz
1/f corner frequency = 100 Hz
AV = 2000
Measurement time = 100 sec
Bandwidth = 2 Hz
This example will result in about 2.2 mVPP (1.9 LSB) of output noise contribution due to the op amp alone,
compared to about 594 μVPP (less than 0.5 LSB) when that op amp is replaced with the LMP2014 which has
no 1/f contribution. If the measurement time is increased from 100 seconds to 1 hour, the improvement
realized by using the LMP2014 would be a factor of about 4.8 times (2.86 mVPP compared to 596 μV when
LMP2014 is used) mainly because the LMP2014 accuracy is not compromised by increasing the observation
time.
d. Copper leadframe construction minimizes any thermocouple effects which would degrade low level/high gain
data conversion application accuracy (see discussion under " The Benefits of the LMP2014" section above).
e. Rail-to-Rail output swing maximizes the ADC dynamic range in 5-Volt single-supply converter applications.
Below are some typical block diagrams showing the LMP2014 used as an ADC amplifier.
Figure 36.
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REVISION HISTORY
Changes from Revision A (March 2013) to Revision B
Page
•
Changed layout of National Data Sheet to TI format .......................................................................................................... 15
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PACKAGE OPTION ADDENDUM
www.ti.com
10-Dec-2020
PACKAGING INFORMATION
Orderable Device
Status Package Type Package Pins Package
Eco Plan
Lead finish/
Ball material
MSL Peak Temp
Op Temp (°C)
Device Marking
Samples
Drawing
Qty
(1)
(2)
(3)
(4/5)
(6)
LMP2014MT/NOPB
LMP2014MTX/NOPB
ACTIVE
TSSOP
TSSOP
PW
14
14
94
RoHS & Green
SN
Level-1-260C-UNLIM
Level-1-260C-UNLIM
0 to 70
0 to 70
LMP20
14MT
ACTIVE
PW
2500 RoHS & Green
SN
LMP20
14MT
(1) The marketing status values are defined as follows:
ACTIVE: Product device recommended for new designs.
LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect.
NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in a new design.
PREVIEW: Device has been announced but is not in production. Samples may or may not be available.
OBSOLETE: TI has discontinued the production of the device.
(2) RoHS: TI defines "RoHS" to mean semiconductor products that are compliant with the current EU RoHS requirements for all 10 RoHS substances, including the requirement that RoHS substance
do not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered at high temperatures, "RoHS" products are suitable for use in specified lead-free processes. TI may
reference these types of products as "Pb-Free".
RoHS Exempt: TI defines "RoHS Exempt" to mean products that contain lead but are compliant with EU RoHS pursuant to a specific EU RoHS exemption.
Green: TI defines "Green" to mean the content of Chlorine (Cl) and Bromine (Br) based flame retardants meet JS709B low halogen requirements of <=1000ppm threshold. Antimony trioxide based
flame retardants must also meet the <=1000ppm threshold requirement.
(3) MSL, Peak Temp. - The Moisture Sensitivity Level rating according to the JEDEC industry standard classifications, and peak solder temperature.
(4) There may be additional marking, which relates to the logo, the lot trace code information, or the environmental category on the device.
(5) Multiple Device Markings will be inside parentheses. Only one Device Marking contained in parentheses and separated by a "~" will appear on a device. If a line is indented then it is a continuation
of the previous line and the two combined represent the entire Device Marking for that device.
(6)
Lead finish/Ball material - Orderable Devices may have multiple material finish options. Finish options are separated by a vertical ruled line. Lead finish/Ball material values may wrap to two
lines if the finish value exceeds the maximum column width.
Important Information and Disclaimer:The information provided on this page represents TI's knowledge and belief as of the date that it is provided. TI bases its knowledge and belief on information
provided by third parties, and makes no representation or warranty as to the accuracy of such information. Efforts are underway to better integrate information from third parties. TI has taken and
continues to take reasonable steps to provide representative and accurate information but may not have conducted destructive testing or chemical analysis on incoming materials and chemicals.
TI and TI suppliers consider certain information to be proprietary, and thus CAS numbers and other limited information may not be available for release.
In no event shall TI's liability arising out of such information exceed the total purchase price of the TI part(s) at issue in this document sold by TI to Customer on an annual basis.
Addendum-Page 1
PACKAGE OPTION ADDENDUM
www.ti.com
10-Dec-2020
Addendum-Page 2
PACKAGE MATERIALS INFORMATION
www.ti.com
9-Apr-2022
TAPE AND REEL INFORMATION
*All dimensions are nominal
Device
Package Package Pins
Type Drawing
SPQ
Reel
Reel
A0
B0
K0
P1
W
Pin1
Diameter Width (mm) (mm) (mm) (mm) (mm) Quadrant
(mm) W1 (mm)
LMP2014MTX/NOPB
TSSOP
PW
14
2500
330.0
12.4
6.95
5.6
1.6
8.0
12.0
Q1
Pack Materials-Page 1
PACKAGE MATERIALS INFORMATION
www.ti.com
9-Apr-2022
*All dimensions are nominal
Device
Package Type Package Drawing Pins
TSSOP PW 14
SPQ
Length (mm) Width (mm) Height (mm)
356.0 356.0 35.0
LMP2014MTX/NOPB
2500
Pack Materials-Page 2
PACKAGE MATERIALS INFORMATION
www.ti.com
9-Apr-2022
TUBE
*All dimensions are nominal
Device
Package Name Package Type
PW TSSOP
Pins
SPQ
L (mm)
W (mm)
T (µm)
B (mm)
LMP2014MT/NOPB
14
94
495
8
2514.6
4.06
Pack Materials-Page 3
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