LP8863-Q1 [TI]
具有 6 个 150mA 通道的 LP8863-Q1 汽车显示屏 LED 背光驱动器;型号: | LP8863-Q1 |
厂家: | TEXAS INSTRUMENTS |
描述: | 具有 6 个 150mA 通道的 LP8863-Q1 汽车显示屏 LED 背光驱动器 驱动 驱动器 |
文件: | 总92页 (文件大小:3815K) |
中文: | 中文翻译 | 下载: | 下载PDF数据表文档文件 |
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LP8863-Q1
ZHCSGN5B –MARCH 2017–REVISED JULY 2018
LP8863-Q1 具有 6 个 150mA 通道的汽车显示 LED 背光驱动器
1 特性
2 应用
1
•
符合汽车类应用的 要求
•
为以下应用提供背光:
•
具有符合 AEC-Q100 标准的下列特性:
–
–
–
–
–
–
汽车信息娱乐系统
汽车仪表盘
–
器件温度 1 级:-40℃ 至 +125℃ 的环境运行温
度范围
智能车镜
•
•
输入电压工作范围:3V 至 48V
抬头显示屏 (HUD)
中央信息显示屏 (CID)
音视频导航 (AVN)
六路高精度电流阱
–
–
电流匹配度为 1%(典型值)
使用 152Hz LED 输出 PWM 频率时,调光比为
32000:1
3 说明
–
–
–
使用 SPI、I2C 或 PWM 输入时,最高 16 位
LED 调光分辨率
LP8863-Q1 是带有升压控制器的汽车高效 LED 驱动
器。六路高精度电流阱支持相移,它可根据使用的通道
数自动调整。可通过 SPI 或 I2C 接口单独和全局控制
电流阱亮度;也可以通过 PWM 输入全局控制亮度。
自动检测使用过的 LED 灯串并调整 LED 通道
相移
每个通道的独立电流控制
升压控制器具有基于 LED 电流阱余量电压的自适应输
出电压控制。该特性可在所有条件下将电压调节到能够
满足需要的最低水平,从而更大限度降低功耗。凭借宽
范围可调频率,LP8863-Q1 能够避免 AM 无线电频带
的干扰。
•
•
混合 PWM 和电流调光功能
最高 47V 输出电压升压或 SEPIC 直流/直流控制器
–
–
–
–
–
开关频率:300kHz 至 2.2MHz
升压扩频功能可降低 EMI
升压同步输入以从外部时钟设置升压开关频率
集成电荷泵支持低 VIN 条件,如冷启动
禁用升压时,输出电压自动放电
LP8863-Q1 支持内置混合 PWM 和电流调光,从而降
低了 EMI、延长了 LED 使用寿命并提高了总光学效
率。
•
详尽的故障诊断
器件信息(1)
简化原理图
D1
器件编号
LP8863-Q1
封装
封装尺寸(标称值)
RISENSE
Q2
L1
VIN
VOUT
HTSSOP (38)
9.70mm x 4.40mm
CIN
COUT
RSD
(1) 要了解所有可用封装,请见数据表末尾的可订购产品附录。
CPUMP
RFB1
RFB2
CPUMP
CPUMP
Q1
GD
GD
ISNS
系统效率
C1N
C1P
PGND
C2x
RSENSE
PGND
95
ISNSGND
VDD
CVDD
FB
VDD
DISCHARGE
GND
VLDO
90
85
CLDO
LED0
LED1
LED2
LED3
LP8863-Q1
VDDIO
IFSEL
EN
INT
SDO_PWM
SDI_SDA
SCLK_SCL
LED4
LED5
ISET
80
75
VOUT = 29 V
VOUT = 36 V
VOUT = 42 V
VOUT = 46 V
SS_ADDRSEL
BST_SYNC
RISET
PWM_FSET
BST_FSET
RPWM_FSET
RBST_FSET
Copyright © 2017, Texas Instruments Incorporated
0
10
20
30
40
50
60
70
80
90 100
Brightness (%)
D007
1
An IMPORTANT NOTICE at the end of this data sheet addresses availability, warranty, changes, use in safety-critical applications,
intellectual property matters and other important disclaimers. PRODUCTION DATA.
English Data Sheet: SNVSAB6
LP8863-Q1
ZHCSGN5B –MARCH 2017–REVISED JULY 2018
www.ti.com.cn
目录
7.16 Typical Characteristics.......................................... 13
Detailed Description ............................................ 14
8.1 Overview ................................................................. 14
8.2 Functional Block Diagram ....................................... 15
8.3 Feature Description................................................. 16
8.4 Device Functional Modes........................................ 38
8.5 Programming .......................................................... 42
8.6 Register Maps......................................................... 46
Application and Implementation ........................ 68
9.1 Application Information............................................ 68
9.2 Typical Applications ................................................ 68
1
2
3
4
5
6
7
特性.......................................................................... 1
应用.......................................................................... 1
说明.......................................................................... 1
修订历史记录 ........................................................... 2
Device Comparison Table..................................... 4
Pin Configuration and Functions......................... 5
Specifications......................................................... 7
7.1 Absolute Maximum Ratings ...................................... 7
7.2 ESD Ratings.............................................................. 7
7.3 Recommended Operating Conditions....................... 7
7.4 Thermal Information.................................................. 8
7.5 Electrical Characteristics........................................... 8
7.6 Protection Electrical Characteristics ......................... 8
8
9
10 Power Supply Recommendations ..................... 81
11 Layout................................................................... 82
11.1 Layout Guidelines ................................................. 82
11.2 Layout Example .................................................... 83
12 器件和文档支持 ..................................................... 84
12.1 器件支持................................................................ 84
12.2 接收文档更新通知 ................................................. 84
12.3 社区资源................................................................ 84
12.4 商标....................................................................... 84
12.5 静电放电警告......................................................... 84
12.6 术语表 ................................................................... 84
13 机械、封装和可订购信息....................................... 84
7.7 LED Current Sink and LED PWM Electrical
Characteristics ........................................................... 9
7.8 Power-Line FET and RISENSE Electrical
Characteristics ........................................................... 9
7.9 Input PWM Electrical Characteristics...................... 10
7.10 Boost Converter Electrical Characteristics............ 10
7.11 Oscillator ............................................................... 11
7.12 Charge Pump........................................................ 11
7.13 Logic Interface Characteristics.............................. 11
7.14 Timing Requirements for SPI Interface................. 12
7.15 Timing Requirements for I2C Interface ................ 12
4 修订历史记录
注:之前版本的页码可能与当前版本有所不同。
Changes from Revision A (June 2017) to Revision B
Page
•
•
已添加 TI 参考设计顶部导航链接............................................................................................................................................ 1
Added note "When internal charge pump is disabled and CPUMP pin is used as an input, max rating is 5.5 V same
as VDD." ................................................................................................................................................................................ 7
•
Added note "When internal charge pump is disabled and CPUMP pin is used as an input, max rating is 5.5V same
as VDD." ................................................................................................................................................................................ 7
•
•
•
•
•
•
•
•
•
•
•
•
•
•
•
•
Deleted "ƒOSC" row ................................................................................................................................................................. 8
Deleted "led_driver_headroom = 01b" .................................................................................................................................. 9
Changed to "325" from "200" ................................................................................................................................................. 9
Changed to "450" from "400" ................................................................................................................................................. 9
Changed to "18.6" from "18.8" ............................................................................................................................................. 11
Changed to "21.4" from "21.2" ............................................................................................................................................. 11
Added VSDOOL and VSDOOH two rows................................................................................................................................ 11
已更改 Data hold time to rising edge of SCLK in SPI Timing Diagram ............................................................................... 12
已更改 to "VDD" from "EN" .................................................................................................................................................. 14
已更改 to "90%" from "88%" ................................................................................................................................................ 18
已更改 to "1.21 V" from "1.2 V" ........................................................................................................................................... 19
已更改 to "1.21 V" from "1.2 V" ........................................................................................................................................... 20
已更改 to "1.76 V" from "1.423 V" ....................................................................................................................................... 20
已更改 to "1.21 V" from "1.2 V" ........................................................................................................................................... 21
已更改 to "ISEL_MAX" from "ISEL_MAX" ................................................................................................................................. 22
已更改 to "1.21 V and 2560" from "1.2 V and 2580" in 公式 11........................................................................................... 24
2
版权 © 2017–2018, Texas Instruments Incorporated
LP8863-Q1
www.ti.com.cn
ZHCSGN5B –MARCH 2017–REVISED JULY 2018
修订历史记录 (接下页)
•
•
•
•
已更改 to "DITHER_SELECT[2:0]" from "DITHER_SELECT[1:0]" ...................................................................................... 29
已更改 to "110 ms" from "1600 milliseconds" ...................................................................................................................... 34
已更改 to "overcurrent" from "undervoltage" ....................................................................................................................... 34
已更改 to "Boost does not start up. Fault is cleared by VDD cycling with correct resistor connection at FSET pin."
from "Device starts up using fail-safe values." .................................................................................................................... 36
•
•
•
已更改 to "400-ms" from "300-ms" ...................................................................................................................................... 39
已更改 to "VDD" from "EN" .................................................................................................................................................. 39
已添加 " For proper operation of discharge function, pull the EN pin before VDD pin. VIN and VDDIO can be set low
any time after EN low." ........................................................................................................................................................ 41
•
•
•
•
•
•
•
•
•
•
•
•
•
•
•
•
•
•
•
•
•
•
•
Changed to "8B0h' from "B0h" ............................................................................................................................................ 49
Changed to "R/W-2h' from 'R/W-0h" ................................................................................................................................... 49
Changed to "2h" from "0h" ................................................................................................................................................... 49
Changed to "100h" from "0h" ............................................................................................................................................... 57
Changed to "100h" from "0h" ............................................................................................................................................... 57
Changed to "100h" from "0h" ............................................................................................................................................... 57
Changed to "100h" from "0h" ............................................................................................................................................... 58
Changed to "000h - 0FFh = 0 °C to 255 °C, 100h - 1FFh = –256 °C to –1 °C" from "0h = –1 to –255 °C" ........................ 58
Changed to "000h - 0FFh = 0 °C to 255 °C, 100h - 1FFh = –256 °C to –1 °C" from "0h = –1 to –255 °C" ....................... 58
Changed to "000h - 0FFh = 0 °C to 255 °C, 100h - 1FFh = –256 °C to –1 °C" from "0h = –1 to –255 °C" ....................... 58
Changed to "1C0h" from "0h" .............................................................................................................................................. 63
Changed to "1C0h" from "0h" .............................................................................................................................................. 63
Changed to "1C0h" from "0h" .............................................................................................................................................. 63
Changed to "1C0h" from "0h" .............................................................................................................................................. 64
Changed to "2882h" from "882h" ......................................................................................................................................... 64
Changed to "2h" from "0h" ................................................................................................................................................... 64
Changed to "2h" from "0h" ................................................................................................................................................... 64
Changed Description of FSM_LIVE_STATUS .................................................................................................................... 65
已更改 to "VIN(min) × D / ( ƒSW × L )" from "VIN(min)× D / ƒSW × L" ........................................................................................... 70
已更改 to "Current set resistor for 100 mA maximum" from "Maximum current set resistor" ............................................. 73
已更改 to "43.5 V" from "40 V" ............................................................................................................................................ 75
已更改 to "10-µF" from "10-µH" ........................................................................................................................................... 78
已更改 to "Current set resistor for 150 mA max" from "Maximum current set resistor" ...................................................... 80
Changes from Original (March 2017) to Revision A
Page
•
首次公开发布的完整产品说明书 ............................................................................................................................................. 1
Copyright © 2017–2018, Texas Instruments Incorporated
3
LP8863-Q1
ZHCSGN5B –MARCH 2017–REVISED JULY 2018
www.ti.com.cn
5 Device Comparison Table
LP8863-Q1
LP8860-Q1
LP8862-Q1
LP8861-Q1
TPS61193-Q1
TPS61194-Q1
TPS61196-Q1
VIN range
3 V to 48 V
3 V to 48 V
4.5 V to 45 V
4.5 V to 45 V
4.5 V to 45 V
4.5 V to 45 V
8 V to 30 V
Number of LED
channels
6
4
2
4
3
4
6
LED current /
channel
150 mA
150 mA
160 mA
100 mA
100 mA
100 mA
200 mA
I2C/SPI support
SEPIC support
Yes
Yes
Yes
No
No
No
No
No
No
No
Yes
Yes
Yes
Yes
4
Copyright © 2017–2018, Texas Instruments Incorporated
LP8863-Q1
www.ti.com.cn
ZHCSGN5B –MARCH 2017–REVISED JULY 2018
6 Pin Configuration and Functions
DCP Package
38-Pin HTSSOP
Top View
VDD
SD
1
2
3
4
5
6
7
8
9
38 GND
37
36 NC
VLDO
VSENSE_N
35
34
NC
VSENSE_P
C1N
PWM_FSET
33 BST_FSET
C1P
CPUMP
CPUMP
32
31
30
29
28
SS_ADDRSEL
SCLK_SCL
SDI_SDA
GD
SDO_PWM
BST_SYNC
GD 10
PGND 11
PGND 12
27 IFSEL
INT
ISNSGND 13
26
25
24
23
14
15
16
17
ISNS
FB
VDDIO
EN
DISCHARGE
LED5
ISET
22 LED0
21 LED1
20 LED2
Exposed Pad
(GND_LED)
LED4 18
LED3 19
Copyright © 2017–2018, Texas Instruments Incorporated
5
LP8863-Q1
ZHCSGN5B –MARCH 2017–REVISED JULY 2018
www.ti.com.cn
Pin Functions
PIN
TYPE
DESCRIPTION
NO.
NAME
Power input for LDO, charge pump, and analog blocks - a 4.7–µF decoupling capacitor is
recommended.
1
VDD
Power
2
3
4
5
6
SD
VSENSE_N
VSENSE_P
C1N
Analog
Analog
Analog
Analog
Analog
Power line FET control. If unused, leave this pin floating.
Pin for input current sense. If input current sense is not used tie to VSENSE_P.
Pin for OVP/UVLO protection and input current sense.
Negative pin for charge pump flying capacitor. If feature not used, leave this pin floating.
Positive pin for charge pump flying capacitor. If feature not used, leave this pin floating.
C1P
Charge pump output pin. If charge pump is not used connect to VDD. TI recommends a
10–µF decoupling capacitor.
7
CPUMP
Power
8
CPUMP
GD
Power
Analog
Analog
Ground
Ground
Ground
Analog
Analog
Analog
Analog
Analog
Analog
Analog
Analog
Analog
Analog
Input
Charge pump output pin. If charge pump is not used connect to VDD.
Gate driver output for boost FET
9
10
11
12
13
14
15
16
17
18
19
20
21
22
23
24
25
GD
Gate driver output for boost FET
PGND
PGND
ISNSGND
ISNS
Power ground
Power ground
Current sense resistor GND of boost controller
Boost current sense pin
FB
Boost feedback input
DISCHARGE
LED5
LED4
LED3
LED2
LED1
LED0
ISET
Boost output voltage discharge pin. Leave floating if unused.
LED current sink output. If unused tie to ground.
LED current sink output. If unused tie to ground.
LED current sink output. If unused tie to ground.
LED current sink output. If unused tie to ground.
LED current sink output. If unused tie to ground.
LED current sink output. If unused tie to ground.
LED current setting input
EN
Enable input
VDDIO
Power
Supply input for digital IO pins - a 4.7–µF decoupling capacitor is recommended.
LP8863-Q1 device fault interrupt output, open drain. Requires an external pullup resistor to
VDDIO - a 10-kΩ pullup resistor is recommended.
26
27
28
INT
Output
Input
IFSEL
Serial control interface selection: low = SPI, high = I2C
Input for synchronizing boost. When synchronization is not used, connect this pin to ground
to disable spread spectrum or to VDDIO to enable spread spectrum.
BST_SYNC
Input
IFSEL=GND, slave data output for SPI. IFSEL=VDDIO, PWM input for brightness control. Tie
to GND if unused.
29
SDO_PWM
Input/Output
30
31
32
33
34
35
36
SDI_SDA
SCLK_SCL
SS_ADDRSEL
BST_FSET
PWM_FSET
NC
Input
Input
Input
Analog
Analog
N/A
IFSEL=GND, slave data input for SPI; IFSEL=VDDIO, serial data for I2C
IFSEL=GND, serial clock for SPI; IFSEL=VDDIO, serial clock for I2C
IFSEL=GND, slave select for SPI; IFSEL=VDDIO, I2C address selection
Resistor for setting boost FSW frequency. Do not leave floating.
Resistor for setting LED PWM frequency. Do not leave floating.
No connect — leave floating.
NC
N/A
No connect — leave floating.
Internal 1.8-V LDO output. Connect bypass capacitor to this pin - a 10–µF decoupling
capacitor is recommended.
37
VLDO
Power
38
GND
Ground
Ground
Ground for LDO — charge pump and analog blocks
LED ground connection
DAP
GND_LED
6
Copyright © 2017–2018, Texas Instruments Incorporated
LP8863-Q1
www.ti.com.cn
ZHCSGN5B –MARCH 2017–REVISED JULY 2018
7 Specifications
7.1 Absolute Maximum Ratings
over operating free-air temperature range (unless otherwise noted)(1)
MIN
-0.3
-0.3
MAX
50
UNIT
V_SENSE_P, VSENSE_N, SD, LED0 to LED5, FB, DISCHARGE
V
Voltage on pins
VDD, EN, ISNS
5.5
VDDIO, SCLK_SCL, SDI_SDA, SDO_PWM, SS_ADDRSEL, INT,
IFSEL, BST_FSET, PWM_FSET, ISET
-0.3
3.6
Voltage on pins
V
(2)
C1P, C1N, CPUMP , GD
-0.3
-0.3
12
2
VLDO
Thermal
Continuous power dissipation
Internally
limited
Internally
limited
Ambient temperature
-40
-40
125
150
260
150
°C
°C
°C
°C
Junction temperature
Maximum lead temperature (soldering)
Storage temperature, Tstg
-65
(1) Stresses beyond those listed under Absolute Maximum Ratings may cause permanent damage to the device. These are stress ratings
only, which do not imply functional operation of the device at these or any other conditions beyond those indicated under Recommended
Operating Conditions. Exposure to absolute-maximum-rated conditions for extended periods may affect device reliability.
(2) When internal charge pump is disabled and CPUMP pin is used as an input, maximum rating is 5.5 V same as VDD.
7.2 ESD Ratings
VALUE
±2000
±500
UNIT
Human body model (HBM), per AEC Q100-002,(1)
Charged-device model (CDM), per AEC Q100-011
Electrostatic
discharge
V(ESD)
All pins
V
Corner pins
±750
(1) AEC Q100-002 indicates that HBM stressing shall be in accordance with the ANSI/ESDA/JEDEC JS-001 specification.
7.3 Recommended Operating Conditions
over operating free-air temperature range (unless otherwise noted). All voltages are with respect to the potential at the GND
pins.
MIN
3
NOM
MAX
48
UNIT
V_SENSE_P, VSENSE_N, SD
Voltage on pins
EN, ISNS
12
V
0
48
0
5.5
5.5
VDD
2.7
3.3/5
Voltage on pins
VDDIO, SCLK_SCL, SDI_SDA, SDO_PWM, SS_ADDRSEL,
INT, IFSEL, BST_FSET, PWM_FSET, ISET
1.65
1.8/3.3
3.6
VLDO
0
0
1.8
2
11
(1)
C1P, C1N, CPUMP , GD
6.6/10
Thermal
Ambient temperature
-40
125
°C
(1) When internal charge pump is disabled and CPUMP pin is used as an input, maximum rating is 5.5 V same as VDD.
Copyright © 2017–2018, Texas Instruments Incorporated
7
LP8863-Q1
ZHCSGN5B –MARCH 2017–REVISED JULY 2018
www.ti.com.cn
7.4 Thermal Information
LP8863
THERMAL METRIC(1)
DCP (HTSSOP)
UNIT
38 PINS
32.4
19.5
8.8
RθJA
Junction-to-ambient thermal resistance
Junction-to-case (top) thermal resistance
Junction-to-board thermal resistance
°C/W
°C/W
°C/W
°C/W
°C/W
°C/W
RθJC(top)
RθJB
ψJT
Junction-to-top characterization parameter
Junction-to-board characterization parameter
Junction-to-case (bottom) thermal resistance
0.3
ψJB
8.9
RθJC(bot)
2.7
(1) For more information about traditional and new thermal metrics, see the Semiconductor and IC Package Thermal Metrics application
report.
7.5 Electrical Characteristics
Limits apply over the full operating ambient temperature range -40°C ≤ TA ≤ +125°C, Unless otherwise specified, VDD = 3.3V,
VIN = 12V, VDDIO = 1.8V
PARAMETER
TEST CONDITIONS
VDD < VPOR, EN = L
MIN
TYP
0.3
75
MAX
2
UNIT
μA
Shutdown mode current, VDD pin
Standby mode current, VDD pin
VDD > VPOR, EN = L
300
μA
LP8863-Q1 enabled, boost enabled
IQ
(ILED = 150mA), CP enabled, VDD
3.3V, fSW = 300kHz, Boost FET -
IPD25N06S4L-30
=
Active mode current , VDD pin
Power-on reset threshold
15
40(1)
2.65
mA
V
VPOR
VDD pin voltage.
(1) Ensured by design.
7.6 Protection Electrical Characteristics
Limits apply over the full operating ambient temperature range –40°C ≤ TA ≤ +125°C, Unless otherwise specified, VDD = 3.3 V,
VIN = 12 V, VDDIO = 1.8 V.
PARAMETER
TEST CONDITIONS
VDD falling
MIN
TYP
2.7
MAX
UNIT
V
VDDUVLO
VDD UVLO threshold
2.6
2.8
VDDUVLO_ VDD UVLO hysteresis
0.1
V
H
VINUVLO
VINUVLO_H VIN UVLO hysteresis
VINOVP VIN OVP threshold
VINOVP _H VIN OVP hysteresis
VIN UVLO threshold
VIN falling
2.7
40.8
155
2.8
0.35
43
2.9
45.2
175
V
V
VIN rising
V
2.5
V
TTSD
Thermal shutdown threshold
Temperature rising
165
°C
°C
Temperature falling from TSD
threshold
TTSD_H
Thermal shutdown hysteresis
20
TTWR_H
TTWR_L
VDDIO
Thermal high warning threshold
Thermal low warning threshold
VDDIO supply voltage
temperature_limit_high = 0x07D
temperature_limit_low = 0x069
115
95
125
105
135
115
3.6
°C
°C
V
1.65
VDDIOIQ
VLDO
VDDIO supply current
1
μA
V
LDO output voltage
1.8
8
Copyright © 2017–2018, Texas Instruments Incorporated
LP8863-Q1
www.ti.com.cn
ZHCSGN5B –MARCH 2017–REVISED JULY 2018
7.7 LED Current Sink and LED PWM Electrical Characteristics
Limits apply over the full operating ambient temperature range -40°C ≤ TA ≤ +125°C, Unless otherwise specified, VDD = 3.3 V,
VIN = 12 V, VDDIO = 1.8 V.
PARAMETER
TEST CONDITIONS
MIN
TYP
0.1
MAX UNIT
Outputs LED0 to LED5 = VOUT
45 V, EN = Low
=
ILEAKAGE
Leakage current
2.5
µA
IMAX
Max LED sink current
LED0 to LED5
150
mA
IACC
LED sink current accuracy(1)
LED sink current matching(1)
IOUT = 150 mA, PWM duty =100%
IOUT = 150 mA, PWM duty =100%
IOUT = 150 mA
−4%
4%
3.5%
0.79
IMATCH
VSAT
1%
0.4
(2)
Saturation voltage
V
fPWM_OUT_MIN
Minimum LED PWM output
frequency
0.152
kHz
fPWM_OUT_MAX
DIM
Maximum LED PWM output
frequency
19.5
kHz
Dimming ratio
fPWM_OUT = 152 Hz
32000:1
8000:1
fPWM_OUT = 4.8 kHz with hybrid
dimming
fPWM_OUT = 4.8 kHz
1000:1
0.55
0.5
VHEADROOM
LED sink headroom
V
V
VHEADROOM_HYST
LED sink headroom hysteresis
shorted_led_thresh = 000
shorted_led_thresh = 001
shorted_led_thresh = 010
shorted_led_thresh = 011
shorted_led_thresh = 100
shorted_led_thresh = 101
shorted_led_thresh = 110
shorted_led_thresh = 111
2.6
3.0
3.5
3.8
VLEDSHORT
LED short detection threshold
LED output minimum pulse
V
4.1
4.6
5.2
5.9
tPWM_OUT
200
ns
(1) Output Current Accuracy is the difference between the actual value of the output current and programmed value of this current.
Matching is the maximum difference from the average. For the constant current sinks on the part (LED0 to LED5), the following are
determined: the maximum output current (MAX), the minimum output current (MIN), and the average output current of all outputs (AVG).
Matching number is calculated: (MAX-MIN)/AVG. The typical specification provided is the most likely norm of the matching figure for all
parts. LED current sinks were characterized with 1 V headroom voltage. Note that some manufacturers have different definitions in use.
(2) Saturation voltage is defined as the voltage when the LED current has dropped 10% from the value measured at 1 V.
7.8 Power-Line FET and RISENSE Electrical Characteristics
Limits apply over the full operating ambient temperature range -40°C ≤ TA ≤ +125°C, Unless otherwise specified, VDD = 3.3 V,
VIN = 12 V, VDDIO = 1.8 V.
PARAMETER
TEST CONDITIONS
RISENSE = 20 mΩ
MIN
TYP
11
1
MAX UNIT
IOCP
Input over current threshold
VSENSE_P pin leakage current
VSENSE_N pin leakage current
SD pin leakage current
Power line FET soft start
SD Pull-down current
9.35
12.65
A
ILEAK_VSENSE_P
ILEAK_VSENSE_N
ILEAK_SD
VSENSE_P = 48 V
VSENSE_N = 48 V
VSD = 48 V
µA
µA
µA
ms
µA
1
1
tSOFT_START
ISD
When RISENSE is used
RSD = 20 kΩ
50
325
450
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7.9 Input PWM Electrical Characteristics
Limits apply over the full operating ambient temperature range -40°C ≤ TA ≤ +125°C, Unless otherwise specified, VDD = 3.3V,
VIN = 12V, VDDIO = 1.8V
PARAMETER
TEST CONDITIONS
MIN
TYP
MAX UNIT
fPWM_IN
PWM input frequency
PWM input minimum on time
PWM input resolution
100
20 000
Hz
ns
bit
tPWM_MIN_ON
INPWMRES
200
16
fPWM_IN = 100 Hz
fPWM_IN = 20 kHz
10
7.10 Boost Converter Electrical Characteristics
Limits apply over the full operating ambient temperature range -40°C ≤ TA ≤ +125°C, Unless otherwise specified, VDD = 3.3V,
VIN = 12V, VDDIO = 1.8V
PARAMETER
Input voltage
TEST CONDITIONS
MIN
TYP
MAX
UNIT
VIN
3
48
V
Boost mode (RFBTOP = 910 kΩ, RFBBOT
100 kΩ)
=
20
6
47
24
VOUT
Output voltage
V
SEPIC mode (RFBTOP = 560 kΩ, RFBBOT
170 kΩ)
=
ƒSW
Switching frequency
BST_FSET = 3.93 kΩ
303
400
kHz
BST_FSET = 4.75 kΩ
BST_FSET = 5.76 kΩ
606
BST_FSET = 7.87 kΩ
800
BST_FSET = 11 kΩ
1000
1250
1667
2200
BST_FSET = 17.8 kΩ
BST_FSET = 42.2 kΩ
BST_FSET = 140 kΩ
Boost mode, IOUT = 6 x 150 mA
Boost mode, IOUT = 6 x 85 mA
SEPIC mode
5.5(1)
10(1)
5(1)
11
VOUT/VIN
Max conversion ratio
0.2
9
IMAX
Boost switching current limit
External FET gate drive voltage
RSENSE = 20 mΩ
10
5
A
V
VDD = 5 V +/-10%, CP Disabled
VDD = 3.3 V +/-10%, CP Enabled
VDD = 5 V +/-10%, CP Enabled
4.5
6
5.5
VGD
6.6
10
7.2
9
11
Source, VGD/(GDRDSON + Total resistance
to gate input of SW FET) must not be
higher than 2.5A
RDSON of internal high side FET to
drive gate of external FET
GDRDSONH
GDRDSONL
1.4
Ω
Ω
RDSON of internal low side FET to
drive gate of external FET
Sink, VGD/(GDRDSON + Total resistance to
gate input of SW FET) must not be higher
than 2.5A
0.75
Delay from beginning of boost soft start to
when LED drivers can begin
tSTART-UP
Start-up time
50
ms
TON
Minimum switch on time
Minimum switch off time
120
70
ns
ns
TOFF
BOOST_OVP low threshold at FB
pin
VBST_OVPL
VBST_OVPH
1.423
1.76
V
V
BOOST_OVP high threshold at FB
pin
(1) Ensured by design
10
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7.11 Oscillator
Limits apply over the full operating ambient temperature range -40°C ≤ TA ≤ +125°C, Unless otherwise specified, VDD = 3.3V,
VIN = 12V, VDDIO = 1.8V
PARAMETER
TEST CONDITIONS
MIN
TYP
MAX
UNIT
fOSC
Oscillator frequency
18.6
20
21.4
MHz
7.12 Charge Pump
Limits apply over the full operating ambient temperature range -40°C ≤ TA ≤ +125°C, Unless otherwise specified, VDD = 3.3V,
VIN = 12V, VDDIO = 1.8V
PARAMETER
TEST CONDITIONS
MIN
TYP
MAX
UNIT
fCP
Charge pump switching frequency
387
417
447
kHz
7.13 Logic Interface Characteristics
Limits apply over the full operating ambient temperature range -40°C ≤ TA ≤ +125°C, Unless otherwise specified, VDD = 3.3V,
VIN = 12V, VDDIO = 1.8V
PARAMETER
TEST CONDITIONS
MIN
TYP
MAX
0.4
UNIT
LOGIC INPUT EN
VENIL
VENIH
IENI
Input low level
Input high level
Input current
V
V
1.2
5
5
30
µA
EN pin internal pull-down
resistance
RPDEN
MΩ
LOGIC INPUT SCLK_SCL, SDI_SDA, SS_ADDRSEL, PWM, IF_SEL, BST_SYNC
0.2 x
VDDIO
VIL
VIH
Input low level
Input high level
V
V
0.8 x
VDDIO
II
Input current
5
µA
V
VSDOOL
Output low level
IOUT = 3 mA
0.3
0.5
0.7 x
VDDIO VDDIO
0.9 x
VSDOOH
Output high level
IOUT = –2 mA
V
LOGIC OUTPUT SDA
VSDAOL
Output low level
I = 3 mA
0.3
0.5
1
V
ISDALEAKAGE Output leakage current
LOGIC OUTPUT INT
V = 5.5 V
μA
VINTOL
Output low level
IOUT = 3 mA
0.3
0.5
1
V
IINTLEAK
Output leakage current
μA
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7.14 Timing Requirements for SPI Interface
MIN
100
50
NOM
MAX
UNIT
ns
1
Cycle time
2
Enable lead time
Enable lag time
Clock low time
Clock high time
Data setup time
Data hold time
Disable time
ns
3
50
ns
4
45
ns
5
45
ns
6
20
ns
7
20
ns
8
30
35
ns
9
Data valid
ns
10
Cb
SS inactive time
Bus capacitance
50
5
ns
40
pF
7.15 Timing Requirements for I2C Interface
MIN
NOM
MAX
UNIT
kHz
µs
ƒSCLK
Clock frequency
400
1
2
3
4
5
6
7
8
9
10
Hold time (repeated) START Condition
Clock low time
0.6
1.3
µs
Clock high time
600
600
50
ns
Set-up time for a repeated START condition
Data hold time
ns
ns
Data setup time
100
ns
Rise Time of SDA and SCL
Fall Time of SDA and SCL
Set-up time for STOP condition
Bus free time between a STOP and a START Condition
300
300
ns
ns
600
1.3
ns
µs
SS
t10t
t2t
t1t
7
4
5
3
SCLK
SDI
6
MSB IN
BIT 30
BIT 16
R/W
BIT 15
BIT 1
BIT 1
LSB IN
9
8
High
Impedance
9
SDO
MSBOUT
LSB OUT
Address
Data
图 1. SPI Timing Diagram
SDA
SCL
10
8
7
6
1
7
9
2
8
4
1
5
3
图 2. I2C Timing Diagram
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7.16 Typical Characteristics
Unless otherwise specified: CIN = COUT = 2 × 10-μF ceramic and 2 × 33-μF electrolytic, VDD = 3.3 V, charge pump enabled,
TA = 25°C
100
95
90
85
80
75
100
95
90
85
80
75
70
65
60
VIN = 9 V
VIN = 9 V
VIN = 12 V
VIN = 16 V
VIN = 24 V
VIN = 12 V
VIN = 16 V
VIN = 24 V
0
10
20
30
40
50
60
70
80
90 100
0
10
20
30
40
50
60
70
80
90 100
Brightness (%)
8 LEDs/string
6 strings
Brightness (%)
8 LEDs/string
6 strings
D001
D002
ƒSW = 303 kHz
L1 = 22 µH
150 mA/string
ƒSW = 2.2 MHz
L1 = 10 µH
150 mA/string
图 3. Boost Efficiency
图 4. Boost Efficiency
90
85
80
75
70
65
60
55
85
80
75
70
65
60
55
50
VIN = 6 V
VIN = 12 V
VIN = 17 V
VIN = 6 V
VIN = 12 V
VIN = 17 V
0
10
20
30
40
50
60
70
80
90 100
0
10
20
30
40
50
60
70
80
90 100
Brightness (%)
Brightness (%)
D003
D004
ƒSW = 303 kHz
2 LEDs/string
150 mA/string
6 strings
ƒSW = 2.2 MHz
2 LEDs/string
150 mA/string
6 strings
L1 = 10 µH, L2 = 15 µH
L1 = L2 = 4.7 µH
图 5. SEPIC Efficiency
图 6. SEPIC Efficiency
150
2.5
2.0
1.5
1.0
0.5
0.0
15 mA
25 mA
50 mA
80 mA
120 mA
120
150 mA
90
60
30
0
0
8192 16384 24576 32768 40960 49152 57344 65536
0
8192 16384 24576 32768 40960 49152 57344 65536
Brightness Code
Brightness Code
D005
D006
图 7. Current Linearity
图 8. Current Matching
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8 Detailed Description
8.1 Overview
The LP8863-Q1 device is a high-voltage LED driver for automotive infotainment, clusters, and other automotive
display LED backlight applications. It supports conventional LED backlight applications and cluster-mode
applications requiring independent duty and current control of each channel.
The LP8863-Q1 device uses the PWM input for brightness control by default. Alternatively, the brightness can
also be controlled by I2C or SPI. When two LP8863-Q1 devices are used in the system, individual I2C addresses
can be selected independently with the SS_ADDRSEL pin. In cluster-mode applications each of the six LED
brightness levels can be individually controlled via the I2C or SPI interface.
The boost frequency, LED PWM frequency, and LED string current are configured with external resistors through
the BST_FSET, PWM_FSET, and ISET pins. The INT pin is used to report faults to the system. Fault interrupt
status can be cleared with the I2C, SPI interface, or is cleared on the falling edge of the VDD pin.
The LP8863-Q1 supports pure PWM dimming and hybrid dimming; that is, combined PWM and current
brightness control. By default PWM dimming mode is enabled, but can be changed using the I2C or SPI
interface.
The six LED current drivers provide up to 150 mA per output and can be tied together to support higher current
LEDs. The maximum output current of the LED drivers is set with the ISET resistor and can be optionally scaled
by the LEDx_CURRENT[11:0] register bits with I2C or SPI interfaces. The LED output PWM frequency is set with
a PWM_FSET resistor. The number of connected LED strings is automatically detected, and the device
automatically selects the correct phase shift. For example, if four strings are connected, the LED outputs are
phase shifted by 90 degrees (= 360 / 4); if 6 strings are connected, the LED outputs are phase shifted by 60
degrees (= 360 / 6). Outputs that are not used must be connected to GND. Unused outputs are disabled and
excluded from adaptive voltage and do not generate open/short LED faults. When I2C is available, LED outputs
can be re-configured in cluster mode to support up to 6 individually controlled channels or, alternatively, 3 to 5
channels for a display and 3 to 1 individual channels for indicator lights. In this mode all strings can be connected
to the boost of LP8863-Q1 or an external boost can be used for indicator channels.
A resistor divider connected from VOUT to the FB pin sets the maximum voltage of the boost. For best efficiency
the boost voltage is adapted automatically to the minimum necessary level needed to drive the LED strings by
monitoring all the LED output voltage drops in real time. The switching frequency of the boost regulator can be
set between 300 kHz and 2.2 MHz by the BST_FSET resistor. The boost has a start-up feature that reduces the
peak current from the power-line during start-up. The LP8863-Q1 also can control a power-line FET to reduce
battery leakage when disabled and provide isolation and protection in the event of a fault.
Fault detection features of LP8863-Q1 include:
•
Open-string and shorted LED detection
LED fault detection prevents system overheating in case of open or short in some of the LED strings
–
•
•
•
Boost overcurrent
Boost overvoltage
Device undervoltage protection
–
Threshold sensing from VDD pin
VIN input overvoltage protection (OVP)
Threshold sensing from VSENSE_P pin
VIN input undervoltage protection
Threshold sensing from VSENSE_P pin
VIN input overcurrent protection (OCP)
Threshold sensing across RISENSE resistor
•
•
•
–
–
–
•
•
Thermal shutdown in case of die overtemperature
Die temperature read-out and programmable thermal window detector
14
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8.2 Functional Block Diagram
VSENSE_P
VSENSE_N SD
VDDIO
CPUMP
CPUMP
GD
Powerline FET
Control
GD
PGND
PGND
C1N
C1P
VDD
Charge
Pump
ISNS
+
-
Boost
Controller
ISNSGND
Analog
FB
VLDO
LDO
Discharge
DISCHARGE
Digital
OSC
20 MHz
PWM_FSET
BST_FSET
EEPROM
LED0
LED1
LED2
LED3
LED4
LED5
ISET
6 x LED
Current
Sinks
ADC
EN
INT
Digital Blocks
(FSM, Adaptive
Voltage Control,
Fault Logic, etc.)
BST_SYNC
IFSEL
SS_ADDRSEL
SDO_PWM
SDI_SDA
SCLK_SCL
LED
Current
Setting
SPI / I2C
TEMP
Sensor
Analog Blocks
(VREF, TSD, etc.)
ADC
GND
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8.3 Feature Description
8.3.1 Control Interface
Device control interface includes:
•
•
•
EN is the enable input for the LP8863-Q1 device.
INT is an open-drain fault output (indicating fault condition detection or thermal threshold crossing).
IFSEL is used for selecting between I2C and SPI.
–
–
–
–
–
SPI is a 4-wire interface using SCL, SDI, SDO, and SS pins.
When SPI is selected the brightness must be controlled using the DISP_BRT and BRT_MODE registers.
I2C is a 2-wire interface using SCL and SDA pins.
When I2C is selected, the ADDRSEL pin is used to select between two alternate slave addresses.
When I2C is selected, the BRT_MODE register setting is used to select whether the brightness is
controlled by the DISP_BRT register or PWM input pin. The PWM pin is selected by default so that an I2C
interface is not required.
•
BST_SYNC is used to input an external clock for the boost switching frequency and control the internal boost
clock mode.
–
–
The external clock is auto detected at start-up and, if missing, the internal clock is used.
Optionally, the BST_SYNC can be tied to VDDIO to enable the boost spread spectrum function or tied to
GND to disable it.
•
•
•
ISET pin to set the maximum LED current level per string.
BST_FSET pin to set the boost switching frequency.
PWM_FSET pin to set the LED output PWM dimming frequency.
Control interface is selected with IF_SEL pin according to 表 1.
表 1. Control Interface Selection, SPI or I2C
IF_SEL
VDDIO (1)
GND (0)
SERIAL INTERFACE
I2C
SPI
In I2C mode the ADDRSEL is used to select between two unique slave addresses, and the PWM input may be
used to control the brightness.
8.3.2 Boost Controller
The LP8863-Q1 current-mode-controlled boost DC/DC controller generates the bias voltage for the LEDs. The
boost is a current-mode-controlled topology with an 8-A cycle by cycle current limit. The boost converter senses
the switch current and across the external sense resistor connected between ISNS and ISNSGND. A 25-mΩ
sense resistor results in an 8-A cycle by cycle current limit.. Maximum boost voltage is configured with external
FB-pin resistor divider connected between VOUT and FB. The FB-divider equation is described in Boost Adaptive
Voltage Control.
16
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D1
L1
VIN
VBOOST
CIN
COUT
OCP
ADAPTIVE
VOLTAGE
CONTROL
LIGHT
LOAD
CPUMP
GD
OVP
R
RFB1
FB
R
R
R
-
GM
Q1
RFB2
+
S
GATE
DRIVER
PGND
BOOST OSCILLATOR
BST_FSET
ADC
RBST_FSET
ISNS
OFF/BLANK TIME
PULSE GENERATOR
CURRENT RAMP
GENERATOR
BST_SYNC
RISENSE
MUX
GM
G
ISNS_GND
Copyright © 2017, Texas Instruments Incorporated
图 9. Boost Controller Block Diagram
The boost switching frequency is adjustable from 300 kHz to 2.2 MHz via an external resistor at BST_FSET (see
表 2).
表 2. Boost Frequency Selection
R_BST_FSET (kΩ)
BOOST FREQUENCY (kHz)
3.92
4.75
5.76
7.87
11
303
400
606
800
1000
1250
1667
2200
17.8
42.2
140
8.3.2.1 Boost Adaptive Voltage Control
The LP8863-Q1 boost DC/DC converter generates the bias voltage for the LEDs. During normal operation, boost
output voltage is adjusted automatically based on the LED current sink headroom voltages. This is called
adaptive boost control. The number of used LED outputs is auto detected and only the active LED outputs are
monitored to control the adaptive boost voltage. Any LED strings with open or short faults are also removed from
the adaptive voltage control loop. The LED driver pin voltages are periodically monitored by the control loop and
the boost voltage is raised if any of the LED outputs falls below the low headroom threshold. The boost voltage is
lowered if all the LED outputs are above the high headroom threshold. See 图 10 for how the low and high
headroom thresholds automatically scale based on the LED string current and VSAT level being used.
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LED0-5 PIN
VOLTAGE
Adaptive Control
makes no change
Adaptive Control
makes no change
Adaptive Control
steps voltage down
Adaptive Control
steps voltage up
SHORTED_LED_THRESHOLD
Only one output (LED0)
above threshold
All LED0-5 outputs above
threshold
One output (LED5) below
threshold
LED_DRV_HEADROOM
+0.5v
LED_DRV_HEADROOM
图 10. Adaptive Boost Voltage Control Loop Function
The external resistive divider (RFB1, RFB2) defines both the minimum and maximum adaptive boost voltage levels.
The FB circuit operates the same in boost and SEPIC topologies. Choose maximum boost voltage based on the
maximum LED string voltage specification. Before the LED drivers are active the boost starts up to the initial
boost level. The initial boost voltage is approximately 90% of maximum boost voltage. Once the LED driver
channels are active, the boost output voltage is adjusted automatically based on LED current sink headroom
voltage. The FB pin resistor divider also scales the boost OVP and undervoltage levels.
18
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8.3.2.1.1 FB Divider Using Two-Resistor Method
A typical FB-pin circuit uses a two-resistor divider circuit between the boost output voltage and ground.
VIN
VBOOST
+
BSTOVPH
BSTOVPL
BSTOCP
VOVPH
VOVPL
VUVP
-
+
-
-
+
RFB1
FB
-
COMP
+
RFB2
+
ISEL[10:0]
VBG
-
图 11. Two-Resistor FB Divider Circuit
Maximum boost voltage can be calculated with 公式 1. The maximum boost voltage can be reached during
OPEN string detection or if all LED strings are left disconnected.
VBG
VMAXBOOST = ((
) + ISEL_MAX )) ì RFB1 + VBG
RFB2
where
•
•
•
VBG = 1.21 V
ISEL_MAX = 38.7 µA
RFB2 recommended value is 100 kΩ for boost operation and 170 kΩ for SEPIC operation.
(1)
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50
45
40
35
30
25
20
15
10
5
100
150
200
250
300
350
400
450
500
550
600
650
700
750
800
850
900
950
R_FB1 (kOhm)
RFB2 = 100 kΩ
图 12. Maximum Boost Output Voltage vs. RFB1 Resistor Value
The minimum boost voltage must be less than the minimum LED string voltage. Minimum boost voltage is
calculated with 公式 2:
VBG
VMINBOOST = (
) ì RFB1 + VBG
RFB2
where
•
VBG = 1.21 V
(2)
When the boost OVP_LOW level is reached the boost controller stops switching the boost FET and the
BSTOVPL_STATUS bit is set. The LED drivers are still active during this condition, and the boost resumes
normal switching operation once the boost output level falls. The boost OVP low voltage threshold is calculated
with 公式 3:
V
VBOOST _OVP_LOW = (( OVPL ) + ISEL_MAX ) ì RFB1 + VOVPL
RFB2
where
•
•
VOVPL = 1.423 V
ISEL_MAX = 38.7 µA
(3)
When the boost OVP_HIGH level is reached the boost controller enters fault recovery mode, and the
BSTOVPH_STATUS bit is set. The boost OVP high-voltage threshold is calculated with 公式 4:
V
VBOOST _OVP_HIGH = (( OVPH ) + ISEL_MAX ) ì RFB1 + VOVPH
RFB2
where
•
•
VOVPH = 1.76 V
ISEL_MAX = 38.7 µA
(4)
When the boost UVP level is reached the boost controller starts a 100-ms OCP counter. The LP8863-Q1 device
enters the fault recovery mode and sets the BSTOCP_STATUS bit if the boost voltage does not rise above the
UVP threshold before the timer expires. The boost UVP voltage when adaptive voltage control is at the maximum
output voltage is calculated with 公式 5:
V
VBOOST _UVP = (( UVP ) + ISEL_MAX ) ì RFB1 + VUVP
RFB2
where
•
•
VUVP = 0.886 V
ISEL_MAX = 38.7 µA
(5)
20
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8.3.2.1.2 FB Divider Using Three-Resistor Method
A FB-pin circuit using a three-resistor divider circuit can be used for applications where less than 200-kΩ
resistors are required.
VIN
VBOOST
+
BSTOVPH
BSTOVPL
BSTOCP
VOVPH
VOVPL
VUVP
-
+
-
-
+
RFB1
RFB3
FB
-
COMP
+
RFB2
+
ISEL[10:0]
VBG
-
图 13. Three-Resistor FB Divider Circuit
Maximum boost voltage can be calculated with 公式 6. The maximum boost voltage can be reached during
OPEN string detection or if all LED strings are left disconnected.
»
…
ÿ
»
…
ÿ
»
…
ÿ
Ÿ
⁄
1
VMAXBOOST
=
((I
ì RFB3) + VBG) ì (
)
+ I
ì RFB1 + (ISEL_MAX ì RFB3)+ VBG
Ÿ
SEL_MAX Ÿ
SEL_MAX
RFB2
……
Ÿ
⁄
Ÿ
⁄
where
•
•
•
•
VBG = 1.21 V
ISEL_MAX = 38.7 µA
RFB2 recommended value is 6 kΩ for boost operation and 10 kΩ for SEPIC operation
RFB3 recommended value is 27 kΩ for boost operation and 30 kΩ for SEPIC operation
(6)
The minimum boost voltage must be less than the minimum LED string voltage. Minimum boost voltage is
calculated with 公式 7:
R
VMINBOOST = (VBG ì ( FB1 )) + VBG
RFB2
(7)
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When the boost OVP_LOW level is reached the boost controller stops switching the boost FET, and the
BSTOVPL_STATUS bit is set. The LED drivers are still active during this condition, and the boost resumes
normal switching operation once the boost output level falls. The boost OVP low voltage threshold is calculated
with 公式 8:
»
…
ÿ
»
…
ÿ
»
ÿ
Ÿ
⁄
1
VBOOST_OVP_LOW
=
((I
ì RFB3) + VOVPL) ì (
)
+ I
ì RFB1 + (ISEL_MAX ì RFB3)+ VOVPL
Ÿ
SEL_MAX Ÿ
…
SEL_MAX
RFB2
……
Ÿ
⁄
Ÿ
⁄
where
•
•
VOVPL= 1.423 V
ISEL_MAX = 38.7 µA
(8)
When the boost OVP_LOW level is reached the boost controller enters fault recovery mode, and the
BSTOVPH_STATUS bit is set. The boost OVP high-voltage threshold is calculated with 公式 9:
»
…
ÿ
»
…
ÿ
»
…
ÿ
Ÿ
⁄
1
VBOOST _OVP_HIGH
=
((I
ì RFB3) + VOVPH) ì (
)
+ I
ì RFB1 + (ISEL_MAX ì RFB3)+ VOVPH
Ÿ
SEL_MAX Ÿ
SEL_MAX
RFB2
……
Ÿ
⁄
Ÿ
⁄
where
•
•
VOVPH = 1.76 V
ISEL_MAX = 38.7 µA
(9)
When the boost UVP level is reached the boost controller starts a 100-ms OCP counter. The LP8863-Q1 device
enters the fault recovery mode and sets the BSTOCP_STATUS bit if the boost voltage does not rise above the
UVP threshold before the timer expires. The boost UVP voltage is calculated with 公式 10:
»
…
ÿ
»
…
ÿ
»
…
ÿ
Ÿ
⁄
1
VBOOST_UVP
=
((I
ì RFB3) + VUVP) ì (
)
+ I
ì RFB1 + (ISEL_MAX ì RFB3)+ VUVP
Ÿ
SEL_MAX Ÿ
SEL_MAX
RFB2
……
Ÿ
⁄
Ÿ
⁄
where
•
•
VUVP = 0.886 V
ISEL_MAX = 38.7 µA
(10)
8.3.2.2 Boost Sync and Spread Spectrum
The boost controller can be clocked by an external BST_SYNC signal. If the external synchronization clock
disappears the boost continues operation at the frequency defined by RBST_FSET resistor. If the external sync
clock disappears while the SYNC pin level is low the boost continues operation without spread spectrum. If the
external sync clock disappears, and BST_SYNC pin remains high the boost initially stops switching for
approximately 256 μs and then begins switching with spread spectrum enabled.
If using the external BST_SYNC input, the external frequency must be between 1.2 and 1.5 times higher than the
frequency defined by the RBST_SET resistor.
The boost converter has also an internal spread spectrum function that reduces EMI noise around the switching
frequency and its harmonic frequencies. The internal spread spectrum function modulates the boost frequency
±3% from the central frequency with a 1.875-kHz modulation frequency. The spread-spectrum function cannot be
used when an external synchronization clock is used.
表 3. Boost Synchronization Mode
BST_SYNC PIN LEVEL
Low (GND)
BOOST CLOCK MODE
Spread spectrum disabled
High (VDDIO)
Spread spectrum enabled
300-kHz to 2200-kHz clock frequency
Spread spectrum disabled, external synchronization mode
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8.3.2.3 Boost Output Discharge
When the boost is disabled, the discharge pin typically sinks 30-mA current in order to discharge the boost
output voltage. The boost voltage discharge time depends on output capacitance. The discharge function is
enabled for a maximum of 400 ms or until the output voltage falls below 3.3 V. The discharge state is entered
when the EN pin goes low. If VDD falls below the power-on reset (POR) level, the LP8863-Q1 device exits the
discharge state early and immediately enters the shutdown state. If the discharge feature is unused, leave the
DISCHARGE pin floating.
8.3.3 2X Charge Pump
An integrated 2X charge pump can be used to supply the gate drive for the external FET of the boost controller.
The charge pump is enabled or disabled by automatically detecting the presence of the external C2X capacitor. If
VDD is < 4.5 V then use the charge pump to generate a high-enough gate voltage to drive the external boost
switching FET. To use the charge pump, a 2.2-µF cap is placed between C1N and C1P. If the charge pump is
not required, C1N and C1P must be left unconnected and CPUMP pins tied to VDD. A 10-µF CPUMP capacitor is
used to store energy for the gate driver. The CPUMP capacitor is required to be used in both charge pump
enabled and disabled conditions and must be placed as close as possible to the CPUMP pins. 图 14 and 图 15
show required connections for both use cases.
D1
L1
RISENSE
Q2
VIN
RSD
CIN
COUT
CPUMP
CPUMP
CPUMP
Q1
GD
RFB1
RFB2
GD
ISNS
C1N
RSENSE
PGND
C2X
PGND
LP8863-Q1
ISNSGND
C1P
VDD
VDD
CVDD
FB
图 14. Charge Pump Enabled Circuit
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D
1
RISENSE
L1
Q2
VIN
RSD
CIN
COUT
CPUMP
CPUMP
CPUMP
Q1
GD
RFB1
RFB2
GD
ISNS
C1N
RSENSE
PGND
PGND
LP8863-Q1
ISNSGND
C1P
VDD
VDD
CVDD
FB
图 15. Charge Pump Disabled Circuit
The C2X_STAT status bit shows whether a C2X capacitor was detected. The C2X_INT bit shows status of any
charge pump faults and generates a INT signal. The C2X_INT bit can be used to prevent the charge-pump fault
from causing an interrupt on the INT pin signal.
8.3.4 1.8-V LDO
The internal LDO regulator converts the input voltage at VDD to a 1.8-V output voltage at VLDO pin. The LDO
regulator supplies internal circuitry. Bypass LDO with a ceramic capacitor of at least 4.7-µF capacitance to
ground. Place capacitor as close as possible to the VLDO pin.
8.3.5 LED Current Sinks
8.3.5.1 LED Output Current Setting
The maximum output LED current is set by an external resistor value. The LEDx_CURRENT[11:0] registers can
also be used to individually adjust each string’s current down from this maximum. The default value for all the
LEDx_CURRENT[11:0] registers is the maximum (4095). 公式 11 is used to calculate the current setting of an
individual string:
1.21V
RISET
LEDx _CURRENT[11: 0]
4095
ILEDx =
ì2560ì
(11)
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LED0 Current Sink
LED0
LATCH
DIN
LED0_DAC
LED0_CURRENT[11:0]
DOUT
EXTERNAL
CURRENT
SETTING
ISET
RISET
LATCH
DIN
LED1_DAC
LED2_DAC
LED3_DAC
LED4_DAC
LED5_DAC
LED1 Current Sink
LED2 Current Sink
LED3 Current Sink
LED4 Current Sink
LED5 Current Sink
LED1
LED2
LED3
LED4
LED5
LED1_CURRENT[11:0]
LED2_CURRENT[11:0]
LED3_CURRENT[11:0]
LED4_CURRENT[11:0]
LED5_CURRENT[11:0]
DOUT
DOUT
DOUT
DOUT
DOUT
LATCH
DIN
LATCH
DIN
LATCH
DIN
LATCH
DIN
LOAD_BRT
图 16. LED Driver Current Setting Circuit
The LEDx_CURRENT[11:0] registers updates are also latched by the LOAD_BRT_DB register similar to the
individual brightness registers. This is done so all LED currents can be updated simultaneously. The default
value for all the LEDx_CURRENT[11:0] registers is FFFh.
8.3.5.2 LED Output PWM Clock Generation
The LED PWM frequency is asynchronous from the input PWM frequency. The LED PWM frequency is
generated from the internal 20-MHz oscillator and can be set to eight discrete frequencies from 152 Hz to 19.531
kHz. The PWM dimming resolution is highest when the lowest PWM frequency is used. The PWM_FSET resistor
determines the LED PWM frequency based on 表 4. PWM resolution in 表 4 is with PWM dither disabled.
表 4. LED PWM Frequency Selection
R_PWM_FSET (kΩ)
LED PWM FREQUENCY (Hz)
PWM DIMMING RESOLUTION (bits)
3.92
4.75
5.76
7.87
11
152
305
16 (maximum)
16
15
14
13
12
11
10
610
1221
2441
4883
9766
19 531
17.8
42.2
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8.3.5.3 LED Output String Configuration
The six LED driver channels of the LP8863-Q1 device can automatically support applications using six, five, four,
three, and two LED strings. The driver channels can also be tied together in groups of two, three, or six
channels. This allows the LP8863-Q1 device to drive three 300-mA LED strings, two 450-mA LED strings, or one
900-mA LED string. The LED strings are always appropriately phase shifted for their string configuration. This
reduces the ripple seen at the boost output, which allows smaller output capacitors and reduces audible ringing
in the capacitors. Phase shift increases the load frequency, which can move potential capacitor noise above the
audible band while still keeping PWM frequency low to support a higher dimming ratio.
When the LP8863-Q1 device is first powered on the string configuration is automatically detected and the phases
of each channel configured. The LED string configuration must not be changed unless the LP8863-Q1 is
powered off in shutdown state. The string configurations in 表 5 are valid configurations for auto detection. Any
other detected configuration defaults to 6 channel / 60 degree mode. The detected string configuration can be
read from the LED_STRING_CONF[2:0] register. Tie unused LEDx pins to ground.
表 5. LED Output String Configuration
AUTOMATIC
PHASE SHIFT
CONFIGURATION
LED0
LED1
LED2
LED3
LED4
LED5
6 channels
5 channels
4 channels
3 channels
2 channels
150 mA
150 mA
150 mA
150 mA
150 mA
150 mA
150 mA
150 mA
150 mA
150 mA
150 mA
150 mA
150 mA
150 mA
150 mA
150 mA
150 mA
150 mA
60°
72°
(Tied to GND)
(Tied to GND)
(Tied to GND)
(Tied to GND)
150 mA
(Tied to GND)
90°
150 mA
(Tied to GND) (Tied to GND)
(Tied to GND) (Tied to GND)
120°
180°
(Tied to GND)
3 channels, 300 mA
/channel
300 mA
300 mA
300 mA
120°
(tie LED pins together)
2 channels, 450 mA
/channel
450 mA
450 mA
180°
(tie LED pins together)
1 channel, 900 mA
(tied LED pins together)
900 mA
None
8.3.5.3.1 Independent Cluster Brightness Control Mode
The LP8863-Q1 supports a cluster mode like that found in the LP8860-Q1 LED driver. This mode allows the
brightness of each of the six driver channels to be controlled independently using the I2C or SPI interface. This is
done by using the six CLUSTER_BRTx[15:0] registers, the six LEDx_GROUP registers and the
LED_EXT_SUPPLY[5:0] register.
The LEDx_GROUP registers select which CLUSTER_BRTx or DISP_BRT register is used for each of the six
LED driver channels. The LED_EXT_SUPPLY[5:0] register selects which channels are used by the adaptive
boost voltage control loop. This allows the LP8863-Q1 to drive LED strings that powered with either the
integrated boost controller or external supply. If a LED driver channel is driving a string powered from the boost
then its corresponding LED_EXT_SUPPLY bit should be set to zero. By default all LED_EXT_SUPPLY bits are
0, and all LEDx_GROUP bits are 000.
An example of how the registers would be configured if the application calls for a display backlight with 4 strings
and uses the remaining 2 current sinks to drive indicator LEDs where anodes are supplied externally (not from
the boost of the LP8863-Q1 device) follows:
LED_EXT_SUPPLY[5:0] = 11000b
LED0_GROUP = 000b
LED1_GROUP = 000b
LED2_GROUP = 000b
LED3_GROUP = 000b
LED4_GROUP = 100b
LED5_GROUP = 101b
(LED5 and LED4 use external supply )
(LED0 uses DISP_BRT register)
(LED1 uses DISP_BRT register)
(LED2 uses DISP_BRT register)
(LED3 uses DISP_BRT register)
(LED4 uses CLUSTER_BRT4 register)
(LED5 uses CLUSTER_BRT5 register)
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8.3.6 Brightness Control
The LP8863-Q1 supports global or individual brightness control for each LED string through individual PWM duty
cycle control of the LED0 to LED5 driver channels via I2C/SPI registers. An internal 20-MHz clock is used for
generating PWM outputs.
8.3.6.1 Brightness Control Signal Path
One display brightness path and five individual brightness paths can be used to control the LED driver channel
brightness. The LEDx_GROUP registers select whether the display brightness path or the cluster 1 to 5
brightness paths control each LED output. The BRT_MODE register selects whether the input to the display
brightness path is the PWM input pin or DISP_BRT register. The brightness control signal path diagram is shown
in 图 17.
The display brightness path has sloper and hybrid dimming functions that can be enabled. By default the sloper
function is enabled and hybrid dimming function disabled. Both functions can be controlled using the I2C or SPI
interface. The sloper function is described in Sloper and hybrid dimming is described in Hybrid Dimming.
By default the LP8863-Q1 operates with LED0 to LED5 channels controlled by the display brightness path. To
enable individual LED string brightness control the LEDx_GROUP registers must be reconfigured with the
SPI/I2C interface.
图 17. LP8863-Q1 Brightness Path Diagram
8.3.6.2 Hybrid Dimming
In addition to pure PWM dimming, LP8863-Q1 supports a hybrid-dimming mode. Hybrid dimming combines PWM
and current modes for brightness control for the display brightness path. In hybrid mode PWM dimming is used
for the low range of brightness, and current dimming is used for high brightness levels as shown in 图 18.
Current dimming control enables improved optical efficiency due to increased LED efficiency at lower currents.
PWM dimming control at low brightness levels ensures linear and accurate control.
Hybrid mode can be enabled with the DIMMING_MODE bit in USER_CONFIG1 register. The PWM and current
modes transition threshold can be set at 12.5% or at 0% brightness with the DIMMING_MODE bits. The latter
selection allows for pure current dimming control mode.
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图 18. 12.5% PWM and Current Hybrid Dimming Diagram
8.3.6.3 Sloper
An optional sloper function makes the transition from one brightness value to another optically smooth. By default
the advanced sloper is enabled with a 200-ms linear sloper duration. Transition time between two brightness
values is programmed with the SLOPE_SELECT[2:0] bits (when 000, sloper is disabled). With advanced sloper
enabled the brightness changes are further smoothed to be more pleasing to the human eye. Advanced slope is
enabled with ADV_SLOPE_ENABLE register bit.
Brightness
Sloper Input
Time
Brightness
Sloper Output
Advanced Slope
Linear Slope
Slope Time
Time
图 19. Brightness Sloper
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8.3.6.4 Dither
The number of brightness steps when using LED output PWM dimming is equal to the 20-MHz oscillator
frequency divided by the LED PWM frequency (set by PWM FSET resistor). The PWM duty cycle dither is a
function the LP8863-Q1 uses to increase the number of brightness dimming steps beyond this oscillator clock
limitation. The dither function modulates the LED driver output duty cycle over time to create more possible
average brightness levels. The DITHER_SELECT[2:0] register bits control the level of dither, disabled, 1, 2, or up
to 5 bits using the I2C or SPI interface. By default the dither has 3 bits enabled (default 011b).
When the 1-bit dither is selected, the width of every second PWM pulse is increased by one LSB (one 20-MHz
clock period). When the 3-bit dither is selected, within a sequence of 8 PWM periods the number of pulses with
increased length varies: dither value 000 - all 8 pulses at default length; 001 - one of the 8 pulses is longer; 010 -
two of the 8 pulses are longer, etc., until at 111 seven of the 8 pulses have increased length. 图 20 shows one
example of PWM output dither.
50.003%
100 Hz
Input PWM
1.2 kHz LED
PWM
Without Dither
50%
50%
50%
50%
50%
1.2 kHz LED
PWM
50.006%
50.006%
50%
With 2bit Dither
图 20. PWM Dither Example
The dither block also has an additional mode at low brightness levels when LED PWM duty cycle is less than the
minimum pulse width (that is, less than the LED driver rise time). In this mode the dither block skips full PWM
pulses to reduce the brightness further enabling very high dimming modes. The end result is the LED PWM
frequency is reduced as more and more minimum pulses are skipped or dithered out. This function can be
enabled using the I2C or SPI interface by programming the EN_MIN_PWM_LIMIT bit to 1. 图 21 shows how the
2-bit minimum brightness dithering works.
100 Hz
Input PWM
300 ns = 0.003%
300 ns = 0.003%
200 ns
No
Pulse
200 ns
No
Pulse
305 Hz LED PWM
With Minimum Pulse
Dither
3.2 ms
3.2 ms
3.2 ms
3.2 ms
Average Brightness = 0.003%
图 21. Minimum Brightness Dither Example
8.3.7 Die Temperature Read-Out and Thermal Window Detector
The LP8863-Q1 has two internal thermal sensors: one for protection purposes (device thermal shutdown) and
one for die temperature monitoring. The die temperature monitor block includes a 9-bit ADC to convert the
analog thermal-sensor output to a temperature reading available in the register JUNCTION_TEMPERATURE.
First temperature result is available 2 ms after the activation of the block and conversion rate is 10 Hz. When the
temperature monitor block is disabled register JUNCTION_TEMPERATURE content is –256°C.
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The die temperature monitor also includes a thermal window detector. The TEMPERATURE_LIMIT_HIGH and
TEMPERATURE_LIMIT_LOW bits set the high and low limits for the thermal window. These thresholds have
±1°C hysteresis: TEMPERATURE _LIMIT_HIGH + 1°C for increasing and TEMPERATURE_LIMIT_HIGH – 1°C
for decreasing, for example. If the die temperature increases above the high limit or reduces below the low limit,
a fault interrupt is generated. Die temperature monitor (ADC, thermal sensor, and window detector) can be
disabled to minimize power dissipation in STANDBY mode. The thermal sensor for TSD is always active.
TSD_STATUS
TSD Thermal Sensor
INT
Interrupts
INT
Temperature Monitor
Window Detector
TEMPHIGH_STATUS
TEMPLOW_STATUS
TEMPERATURE_LIMIT_HIGH
TEMPERATURE_LIMIT_LOW
Thermal Sensor
I2C/SPI
JUNCTION_TEMPERATURE
TEMP_MON_EN
ADC
图 22. Thermal Shutdown and Sensor Block Diagram
图 23, 图 24, and 图 25 show the INT pin and status behaviors of the TSD, temperature high, and temperature
low limits.
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Enters Standby Mode
TTSD Thermal Shutdown
Returns to Normal Mode
TTSD_H hysteresis
TEMPERATURE_LIMIT_HIGH
TEMPERATURE_LIMIT_LOW
Host clears INT Status
TEMP_MON_EN
INT
TEMPHIGH_STATUS
TEMPLOW_STATUS
TSD_STATUS
图 23. Thermal Shutdown and Sensor Example 1
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TTSD Thermal Shutdown
TTSD_H hysteresis
TEMPERATURE_LIMIT_HIGH
TEMPERATURE_LIMIT_LOW
Host clears INT Status
TEMP_MON_EN
INT
TEMPHIGH_STATUS
TEMPLOW_STATUS
TSD_STATUS
图 24. Thermal Shutdown and Sensor Example 2
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TTSD Thermal Shutdown
TTSD_H hysteresis
TEMPERATURE_LIMIT_HIGH
TEMPERATURE_LIMIT_LOW
Host clears INT Status
TEMP_MON_EN
INT
TEMPHIGH_STATUS
TEMPLOW_STATUS
TSD_STATUS
图 25. Thermal Shutdown and Sensor Example 3
8.3.8 Protection and Fault Detections
The LP8863-Q1 device includes fault detections for LED open and short conditions, boost input undervoltage,
overvoltage and overcurrent, boost output overvoltage and overcurrent, VDD undervoltage and die
overtemperature. Host can monitor the status of the faults in INTERRUPT_STATUS_1 and
INTERRUPT_STATUS_2 registers.
8.3.8.1 LED Faults
During normal boost operation, boost voltage is raised if any of the LED outputs falls below the low headroom
threshold level. Open LED fault is detected if boost output voltage has reached the maximum and at least one
LED output is still below the threshold. The open string is then disconnected from the boost adaptive control loop
and its output is disabled. Any LED fault sets the status bit LED_STATUS and an interrupt is generated unless
LED interrupt is disabled. Reason for the open LED faults can be read from bits OPEN_LED and LEDx_FAULT
(x = 0...5, indicating the faulty LED) in INTERRUPT_STATUS_2 register. These bits maintain their value until
device power-down while the LED_STATUS bit is cleared by the interrupt clearing procedure. If a new LED fault
is detected, LED_STATUS is set and an interrupt generated again.
Shorted LED fault is detected if one or more LED outputs are above the SHORTED_LED_THRESHOLD setting
and at least one LED output is inside the normal operation widow (see 图 26). Shorted string is disconnected
from the boost adaptive control loop and the LED PWM output is disabled. LED_STATUS status bit is set and an
interrupt generated similarly as in open LED case. Shorted LED fault reason can be read from bits SHORT_LED
and LEDx_FAULT (x = 0...5, indicating the faulty LED) in INTERRUPT_STATUS_2 register.
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图 26. LED Open and Short Detection Logic
8.3.8.2 Boost Faults
Boost overvoltage is detected if the FB pin voltage exceeds the VOVPL threshold. When boost overvoltage is
detected, BSTOVPL_STATUS bit is set in the INTERRUPT_STATUS_1 register. The boost FET stops switching,
and the output voltage is automatically limited. If the BSTOVPL_STATUS bit is continually set (that is, reappears
after clearing), it may indicate an issue in the application. Boost overvoltage low is monitored during device
normal operation (ACTIVE mode).
A second boost overvoltage high fault is detected if the FB pin voltage exceeds the VOVPH threshold. The
LP8863-Q1 device enters the fault recovery state to protect against excessive thermal dissipation caused by high
headroom on the LED drivers. When boost overvoltage is detected, BSTOVPH_STATUS bit is set in the
INTERRUPT_STATUS_1 register. A fault interrupt is also generated. If the BSTOVPH_STATUS bit is continually
set (that is, reappears after clearing), it may indicate an issue in the application. Boost overvoltage high is
monitored during device normal operation (ACTIVE mode).
Boost overcurrent is detected if the FB pin voltage drops below the VUVP threshold. A boost OCP fault is detected
if the undervoltage condition persists for longer than 110 ms. If the boost overcurrent timer expires before the
output voltage recovers, the BSTOCP_STATUS bit is set in the INTERRUPT_STATUS_1 register. The fault
recovery state is entered, and a fault interrupt is generated. If the BSTOCP_STATUS bit is permanently set, it
may indicate an issue in the application. Boost overcurrent is monitored from the boost start, and fault may
trigger during boost start-up.
8.3.8.3 Power-Line Faults
If during operation of the LP8863-Q1 device the VIN (VSENSE_P pin) voltage falls below the VINUVLO falling
level, the boost, LED outputs, and power-line FET are turned off, and the device enters STANDBY mode. The
VINUVLO_STATUS bit is also set, and the INT pin is triggered. When the VINUVLO voltage rises above the
rising threshold level the LP8863-Q1 device exits STANDBY and begins the start-up sequence.
If during LP8863-Q1 device operation VIN (VSENSE_P pin) voltage rises above the VINOVP rising level, boost,
LED outputs, and power-line FET are turned off, and the device enters STANDBY mode. The VINOVP_STATUS
bit is also set, and the INT pin is triggered. When the VINOVP voltage falls below the falling threshold level the
LP8863-Q1 exits STANDBY and begins the start-up sequence.
The VIN OCP protection detects overcurrent by measuring voltage of the RISENSE resistor connected between
VSENSE_P and VSENSE_N pins. VIN OCP sensing begins once the LP8863-Q1 enters the PL FET soft-start
state. Fault is detected if overcurrent condition duration lasts for at least 10 μs, minimum. The VINOCP_STATUS
bit is also set, and the INT pin is triggered. To trip at a lower current limit a larger sense resistor can be used to
create a 220-mV voltage difference across the sense resistor.
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8.3.8.4 VDD Undervoltage Fault
If during LP8863-Q1 device operation VDD falls below VDDUVLO falling level, boost, PL FET, and LED outputs
are turned off, and the device enters STANDBY mode. The VDDUVLO_STATUS fault bit is set, and the INT pin
is triggered. The LP8863-Q1 recovers automatically to ACTIVE mode when VDD rises above VDDUVLO rising
threshold.
If VDD falls below VPOR the LP8863-Q1 device enters SHUTDOWN mode.
8.3.8.5 Thermal Shutdown
If the die temperature of LP8863-Q1 reaches the thermal shutdown threshold TTSD, the boost, PL FET, and LED
outputs on LP8863-Q1 device shut down to protect the device from damage. Fault status bit TSD_STATUS bit is
set, and the INT pin is triggered. The device restarts the PL FET, the boost, and LED outputs when temperature
drops by TTSD_H amount.
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8.3.8.6 Overview of the Fault/Protection Schemes
TRIGGER FAULT
INTERRUPT
ENTER FAULT
RECOVERY
FAULT NAME
STATUS BIT
CONDITION
ACTION
FB pin voltages falls below VUVP level
for > 110 ms
Device goes to standby and then attempts to
restart 200 ms after fault occurs.
Boost overcurrent
BSTOCP_STATUS
Yes
Yes
Boost stops switching until boost voltage level
falls. The device remains in normal mode with
LED drivers operational.
Boost overvoltage low
Boost OVP high
BSTOVPLOW_STATUS FB pin voltages rises above VOVPL level
No
No
Device goes to standby and waits until output
voltage falls below threshold before restarting.
BSTOVPH_STATUS
BSTSYNC_STATUS
FB pin voltages rises above VOVPH level
Yes
Yes
Device is enabled while a valid external
SYNC clock is running. Then SYNC
stops or changes to invalid frequency.
Valid range is 1.2× to 1.5× of frequency
selected by BST_FSET resistor.
Device defaults to internal clock frequency
selected by BST_FSET resistor. If SYNC input is
held high then spread spectrum is enabled. If
SYNC input is held low then spread spectrum is
disabled.
Boost sync clock invalid
No
No
Device goes to standby and waits until output
voltage falls below threshold before restarting.
VIN overvoltage
VIN undervoltage
VINOVP_STATUS
VINUVLO_STATUS
VIN voltage rises above 43 V.
Yes
Yes
No
No
Device goes to standby and then attempts to
restart once the input voltage rises above
threshold.
VIN voltage falls below 2.8 V.
Voltage across RISENSE exceeds 220
mV
Device goes to standby and then attempts to
restart 200 ms after fault occurs.
VIN overcurrent
VINOCP_STATUS
VDDUVLO_STATUS
TSD_STATUS
Yes
Yes
Yes
Yes
No
VDD level falls below VDDUVLO
threshold.
Device restarts once VDD level rises above
VDDUVLO threshold.
VDD undervoltage
Thermal shutdown
Junction temperature rises above TTSD
threshold.
Device goes to standby and then attempts to
restart once die temperature falls below threshold.
No
Headroom voltage on one or more
channels is below minimum level and
boost has adapted to maximum level.
Faulted LED string is disabled and removed from
adaptive boost control loop. String is re-enabled
next power cycle.
LED_STATUS
OPEN_LED
Open LED string
Shorted LED
Yes
Yes
No
No
Headroom voltage on one or more
channels is above the
SHORTED_LED_THRESHOLD for > 5
ms while the headroom of at least one
channel is still below this threshold.
Faulted LED string is disabled and removed from
adaptive boost control loop. String is re-enabled
next power cycle.
LED_STATUS
LED string detection does not match
one of 8 valid configurations
Device defaults to six LED string phase shift
mode. String detection reoccurs next power cycle.
Invalid LED string detected INVSTRING_STATUS
Yes
Yes
No
No
Boost does not start up. Fault is cleared by VDD
cycling with correct resistor connection at FSET
pin.
BST_FSET or PWM_FSET are missing
or an invalid value
FSET detection fault
Charge pump fault
FSET_STATUS
CP_STATUS
Device functions normally, if possible. If charge
pump issue is severe, it is likely boost overcurrent
fault will trip.
Charge pump voltage level is abnormal.
No
No
36
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Device functions normally, if possible. If charge
pump issue is severe, it is likely boost overcurrent
fault will trip.
Charge pump components
missing
CPCAP_STATUS
Charge pump is missing components.
No
No
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8.4 Device Functional Modes
8.4.1 State Diagram
From Any State
VDD < POR
SHUTDOWN
VDD > POR
DEVICE INIT
STANDBY
EN=1
PL FET
SOFTSTART
FAULT RECOVERY
200 ms and
PL_PRECHARGE_READY
50 ms and
PL_PRECHARGE_COMPLETE
BOOST STARTUP
50 ms and
BOOST_OK=0
50 ms and
BOOST_OK=1
FAULT
NORMAL
LATCH FAULT
All LED channels have been
disabled due to open or short faults.
EN=0
DISCHARGE_DONE and
EN=0
DISCHARGE
图 27. State Machine Diagram
8.4.2 Shutdown
When VDD is below POR threshold device is in shutdown state.
8.4.3 Device Initialization
After POR is released device initialization begins. During this state the LDO is started up, EEPROM default and
trim configurations are loaded, BOOST_FSET and PWM_FSET resistors are detected, and the LED string
configuration is detected.
38
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Device Functional Modes (接下页)
8.4.4 Standby Mode
In standby the LP8863-Q1 device can be accessed with I2C or SPI to change any configuration registers. Analog
blocks are disabled to save power.
8.4.5 Power-line FET Soft Start
Power-line FET is enabled, and boost input and output capacitors are charged to VIN level. VIN faults for OCP,
OVP, and UVP are enabled.
8.4.6 Boost Start-Up
Boost voltage is ramped to maximum voltage level with reduced current limit. Start-up exits when boost reaches
initial target voltage. All boost faults are now enabled.
8.4.7 Normal Mode
LED drivers are enabled when brightness is greater than zero. All LED faults are active.
8.4.8 Discharge Mode
When EN goes low from normal mode the boost output voltage is discharged. This state exits when boost
voltage falls below 3.3 V or when the 400-ms timer expires.
8.4.9 Fault Recovery
Non-LED faults can trigger fault recover state. LED drivers, boost converter, and power-line FET are disabled for
200 ms, and the device attempts to restart from standby mode if EN is still high.
8.4.10 Latch Fault
If all LED strings are disabled due to faults then the LP8863-Q1 enters the latch fault mode. This state can be
exited by toggling the VDD pin.
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Device Functional Modes (接下页)
8.4.11 Start-Up Sequence
DEVICE
INIT
PL FET
PRECHARGE
BOOST
SOFTSTART
STATE
VIN
SHUTDOWN
STANDBY
NORMAL
VDD
VDDIO
EN
PWM
Input Pin
VINIT
VADAPT
Boost VOUT
VIN
50 ms
50 ms
LEDx
图 28. Start-Up Sequence Diagram
40
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Device Functional Modes (接下页)
8.4.12 Shutdown Sequence
STATE
VIN
NORMAL
DISCHARGE
SHUTDOWN
VDD
VDDIO
EN
PWM Input
Pin
Boost
VOUT
3.3 V
0 V
LEDx
< 400 ms
图 29. Shutdown Sequence Diagram
For proper operation of discharge function, pull the EN pin before VDD pin. VIN and VDDIO can be set low any
time after EN low.
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8.5 Programming
8.5.1 Serial Interface Selection
The serial interface type is selected by connecting the IFSEL pin to VDDIO or GND. The LP8863-Q1 device
checks the IFSEL pin state as part of device startup. Device start-up occurs after VDD and VDDIO POR levels
are reached. 表 6 shows how to connect the IFSEL pin to select between the SPI and I2C-compatible interfaces.
表 6. Serial Control Interface Selection
PIN NAME
SS_ADDRSEL
SCLK_SCL
SDI_SDA
IFSEL PIN = VDDIO
IFSEL PIN = GND
ADDRSEL
SCL
SS
SCLK
SDI
SDA
SDO_PWM
PWM
SDO
8.5.2 SPI Interface
In SPI mode host can address as many unique LP8863-Q1 devices as there are slave select pins on host. The
complete 10-bit register space in LP8863-Q1 device can be accessed using SPI interface.
The LP8863-Q1 device is compatible with SPI serial-bus specification and operates as a slave device. The
transmission consists of 32-bit write and read cycles. One cycle consists of a 15-bit register address (10 bits
used), 1 read/write (R/W) bit and 16-bit data to maintain compatibility with 16-bit SPI.
The R/W bit high state defines a write cycle and low defines a read cycle. The SDO output is normally in a high-
impedance state. When the slave-select pin SS for the device is active (that is, low) the SDO output is pulled
low. During write cycle SDO stays in high-impedance state. The address and data bits are transmitted MSB first.
The slave-select signal SS must be low during the cycle transmission. SS resets the interface when high, and it
has to be taken high between successive cycles, except when using auto- increment mode. Data is clocked in on
the rising edge of the SCLK clock signal, while data is clocked out on the falling edge of SCLK.
图 30. SPI Write
图 31. SPI Read
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8.5.3 I2C-Compatible Interface
Two LP8863-Q1 slave devices may share the same I2C bus. The SS_ADDRSEL pin selects between the two
possible base slave addresses.
表 7. I2C Address Selection
SS_ADDRSEL PIN
GND
7-BIT I2C BASE SLAVE ADDRESS
0x2C
0x3C
VDDIO
The LP8863-Q1 uses a 10-bit register address space. The 10-bit register address space is accessed as four
separate 8-bit address spaces. Four different slave addresses are used to access each of the four 8-bit address
register spaces.
表 8. I2C Address Registers Selection
SS_ADDRSEL PIN
7-BIT BASE ADDRESS
7-BIT SLAVE ADDRESS
ACCESSIBLE 10-BIT REGISTERS
0x000 to 0x0FF
0x2C
0x2D
0x2E
0x2F
0x3C
0x3D
0x3E
0x3F
0x100 to 0x1FF
GND
0x2C
0x200 to 0x2FF
0x300 to 0x3FF
0x000 to 0x0FF
0x100 to 0x1FF
VDDIO
0x3C
0x200 to 0x2FF
0x300 to 0x3FF
Write I2C transactions are made up of 4 bytes. The first byte includes the 7-bit slave address and Write bit. The
7-bit slave address selects the LP8863-Q1 slave device and one of four 8-bit register address sections. The
second byte includes eight LSB bits of the 10-bit register address. The last two bytes are the 16-bit register
value.
Read I2C transactions are made up of five bytes. The first byte includes the 7-bit slave address and Write bit.
The 7-bit slave address selects the LP8863-Q1 slave device and one of four 8-bit register address sections. The
second byte includes eight LSB bits of the 10-bit register address. The third byte includes the 7-bit slave address
and Read bit. The last two bytes are the 16-bit register value returned from the slave.
图 32. I2C Write
图 33. I2C Read
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8.5.4 Programming Examples
8.5.4.1 General Configuration Registers
The LP8863-Q1 does not require any serial interface configuration. It can be simply controlled with the EN pin
and PWM pin. Most of the device configuration is accomplished using external resistor values or automatic
detection. If a serial interface is available then extended configuration is possible. The configuration registers can
be written in standby state as shown in 表 9.
表 9. Configuration Registers
REGISTER NAME
BRT_MODE
FUNCTION
Selects PWM pin or DISPLAY_BRT register for brightness control.
Selects voltage level for shorted LED Fault.
SHORTED_LED_THRESHOLD
DITHER_SELECT
Selects up to 3 bits of PWM dither for added dimming resolution.
Enables 200-ns PWM pulse limit and frequency dither to reach lower minimum brightness
levels.
EN_MIN_PWM_LIMIT
SLOPE_SELECT
Selects duration for linear brightness sloper.
ADV_SLOPE_ENABLE
DIMMING_MODE
Enables advance sloper S-shape smoothing function.
Select between PWM, hybrid or current LED ouput dimming types.
Enables temperature window monitor function.
TEMP_MON_EN
TEMPERATURE_LIMIT_HIGH
TEMPERATURE_LIMIT_LOW
Sets HIGH threshold level for temperature window function.
Sets LOW threshold level for temperature window function.
8.5.4.2 Clearing Fault Interrupts
The LP8863-Q1 has an INT pin to alert the host when a fault occurs. If a serial interface is available, the Interrupt
Fault Status registers can be read back to learn which fault(s) have been detected. These status bits are located
in the INTERRUPT_STATUS_1, INTERRUPT_STATUS_2, and INTERRUPT_STATUS_3 registers. Each
interrupt status has a STATUS bit and a CLEAR bit. If a fault interrupt has been detected, a 1 is read back from
its STATUS bit. To clear a fault interrupt status a 1 must be written to both the STATUS bit and CLEAR bit at the
same time.
8.5.4.3 Disabling Fault Interrupts
By default most of the LP8863-Q1 faults trigger the INT pin. Each fault has two INT_EN bits. These bits are
located in the INTERRUPT_ENABLE_1, INTERRUPT_ENABLE_2, and INTERRUPT_ENABLE_3 registers. If the
INT_EN bit is read and returns a 1, the INT pin is triggered when that fault occurs. The fault interrupt can be
disabled by writing 01 to its INT_EN bits, or it can be enabled by writing 11 to its INT_EN bits. There is also a
GLOBAL fault interrupt that can be disabled to prevent any faults from triggering the INT pin.
8.5.4.4 Diagnostic Registers
The LP8863-Q1 contains several diagnostic registers than can be read with the serial interface for debugging or
additional device information. 表 10 is a summary of the available registers.
表 10. Diagnostic Registers
REGISTER NAME
JUNCTION_TEMPERATURE
FUNCTION
9-bit die junction temperature in 2s complement form — 1°C per LSB
Current state of the functional state machine
FSM_LIVE_STATUS
PWM_INPUT_STATUS
LED_PWM_STATUS
LED_CURRENT_STATUS
Measured 6-bit duty cycle of the PWM pin input
16-bit LED0 PWM duty cycle from state machine
12-bit LED0 current DAC value from state machine
10-bit value for adaptive boost voltage target — value is linear between
VBOOST_MIN and VBOOST_MAX calculations
VBOOST_STATUS
AUTO_PWM_FREQ_SEL
AUTO_BOOST_FREQ_SEL
AUTO_LED_STRING_CFG
LED PWM frequency value from PWM_FSET detection
Boost switching frequency value from PWM_FSET detection
LED string phase configuration detected from LED pin configuration
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8.5.4.5 Cluster Mode Configuration and Control Registers
The LP8863-Q1 device supports a cluster mode where the duty cycles and LED current of the six LED current
drivers can be controlled independently. This mode can also select which LED current driver’s headroom levels
are used by the adaptive boost voltage control loop. If the anode of an LED string is supplied by an external
supply and not the integrated boost controller then its LED_EXT_SUPPLY bit is set to 1. The cluster mode
configuration registers are summarized in 表 11. More details can be found in Register Maps.
表 11. Cluster Mode Configuration Registers
REGISTER NAME
FUNCTION
LED0_GROUP...LED5_GROUP
Selects which of the five CLUSTERx_BRT or DISPLAY_BRT registers control each
LED current driver.
CLUSTER1_BRT…CLUSTER5_BRT
LED0_CURRENT…LED5_CURRENT
LOAD_BRT_DB
Five 16-bit brightness values that can be used in addition to the DISPLAY_BRT
register.
Six 12-bit current registers allow LED current to be independently scaled from
maximum level for LED current driver.
Load BRT bit is written to 1 in order to update the CLUSTERx_BRT and
LEDx_CURRENT registers at the same time.
LED_EXT_SUPPLY
Six bits to select which LED current driver is powered from an external supply and not
the boost converter.
LED0_SHORT_DISABLE…
LED5_SHORT_DISABLE
Six bits to individually disable LED short detection for each LED current driver. Used if
LED current value is set to lower value than other strings.
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8.6 Register Maps
8.6.1 FullMap Registers
Table 12 lists the memory-mapped registers for the FullMap registers. All register offset addresses not listed in
Table 12 should be considered as reserved locations and the register contents should not be modified.
Table 12. FULLMAP Registers
Offset
20h
Acronym
Register Name
Section
Go
Go
Go
Go
Go
Go
Go
Go
Go
Go
Go
Go
Go
Go
Go
Go
Go
Go
Go
Go
Go
Go
Go
Go
Go
Go
Go
Go
Go
Go
Go
Go
Go
Go
Go
BL_MODE
Brightness Mode
28h
DISP_BRT
Display Brightness
30h
GROUPING1
Brightness Grouping 1
Brightness Grouping 2
User Config 1
32h
GROUPING2
40h
USER_CONFIG1
42h
USER_CONFIG2
User Config 2
4Eh
INTERRUPT_ENABLE_3
INTERRUPT_ENABLE_1
INTERRUPT_ENABLE_2
INTERRUPT_STATUS_1
INTERRUPT_STATUS_2
INTERRUPT_STATUS_3
JUNCTION_TEMPERATURE
TEMPERATURE_LIMIT_HIGH
TEMPERATURE_LIMIT_LOW
CLUSTER1_BRT
Fault Interrupt Enable 3
Fault Interrupt Enable 1
Fault Interrupt Enable 2
Fault Interrupt Status 1
Fault Interrupt Status 2
Fault Interrupt Status 3
Die Junction Temperature
Temperature High Limit
Temperature Low Limit
Cluster 1 Brightness
Cluster 2 Brightness
Cluster 3 Brightness
Cluster 4 Brightness
Cluster 5 Brightness
Cluster Brightness and Current Load Bit
LED0 Current
50h
52h
54h
56h
58h
E8h
ECh
EEh
13Ch
148h
154h
160h
16Ch
178h
1C2h
1C4h
1C6h
1C8h
1CAh
1CCh
288h
28Ah
2A4h
2A6h
2A8h
2AAh
2ACh
2AEh
CLUSTER2_BRT
CLUSTER3_BRT
CLUSTER4_BRT
CLUSTER5_BRT
BRT_DB_CONTROL
LED0_CURRENT
LED1_CURRENT
LED1 Current
LED2_CURRENT
LED2 Current
LED3_CURRENT
LED3 Current
LED4_CURRENT
LED4 Current
LED5_CURRENT
LED5 Current
BOOST_CONTROL
SHORT_THRESH
Boost Control
Shorted LED Threshold
Device State Diagnostics
PWM Input Diagnostics
PWM Output Diagnostics
LED Current Diagnostics
Adaptive Boost Diagnostics
Auto Detect Diagnstics
FSM_DIAGNOSTICS
PWM_INPUT_DIAGNOSTICS
PWM_OUTPUT_DIAGNOSTICS
LED_CURR_DIAGNOSTICS
ADAPT_BOOST_DIAGNOSTICS
AUTO_DETECT_DIAGNOSTICS
Complex bit access types are encoded to fit into small table cells. Table 13 shows the codes that are used for
access types in this section.
Table 13. FullMap Access Type Codes
Access Type
Read Type
R
Code
Description
R
Read
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Table 13. FullMap Access Type Codes (continued)
Access Type
Write Type
W
Code
Description
W
Write
Reset or Default Value
-n
Value after reset or the default
value
8.6.1.1 BL_MODE Register (Offset = 20h) [reset = 300h]
BL_MODE is shown in Figure 34 and described in Table 14.
Return to Summary Table.
Figure 34. BL_MODE Register
15
7
14
6
13
5
12
4
11
10
2
9
1
8
0
RESERVED
R/W-C0h
3
RESERVED
R/W-C0h
brightness_mode
R/W-0h
Table 14. BL_MODE Register Field Descriptions
Bit
Field
Type
Reset
Description
15-2
1-0
RESERVED
R/W
C0h
These bits are reserved.
brightness_mode
R/W
0h
0h = Brightness controlled by PWM Input
1h = Reserved
2h = Brightness controlled by DISPLAY_BRT Register
3h = Reserved
8.6.1.2 DISP_BRT Register (Offset = 28h) [reset = 0h]
DISP_BRT is shown in Figure 35 and described in Table 15.
Return to Summary Table.
Figure 35. DISP_BRT Register
15
14
13
12
11
10
9
8
7
6
5
4
3
2
1
0
DISPLAY_BRT
R/W-0h
Table 15. DISP_BRT Register Field Descriptions
Bit
15-0
Field
DISPLAY_BRT
Type
Reset
Description
R/W
0h
Display Brightness Register
8.6.1.3 GROUPING1 Register (Offset = 30h) [reset = 0h]
GROUPING1 is shown in Figure 36 and described in Table 16.
Return to Summary Table.
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Figure 36. GROUPING1 Register
15
7
14
6
13
5
12
11
10
2
9
1
8
0
LED3_GROUP
R/W-0h
LED2_GROUP
R/W-0h
4
3
LED1_GROUP
R/W-0h
LED0_GROUP
R/W-0h
Table 16. GROUPING1 Register Field Descriptions
Bit
Field
Type
Reset
Description
15-12
11-8
7-4
LED3_GROUP
LED2_GROUP
LED1_GROUP
LED0_GROUP
R/W
0h
LED Output 3 Brightness Control Mapping
0h = DISP_BRT/PWM
1h = CLUSTER1_BRT
2h = CLUSTER3_BRT
3h = CLUSTER3_BRT
4h = CLUSTER4_BRT
5h = CLUSTER5_BRT
R/W
R/W
R/W
0h
0h
0h
LED Output 2 Brightness Control Mapping
0h = DISP_BRT/PWM
1h = CLUSTER1_BRT
2h = CLUSTER3_BRT
3h = CLUSTER3_BRT
4h = CLUSTER4_BRT
5h = CLUSTER5_BRT
LED Output 1 Brightness Control Mapping
0h = DISP_BRT/PWM
1h = CLUSTER1_BRT
2h = CLUSTER3_BRT
3h = CLUSTER3_BRT
4h = CLUSTER4_BRT
5h = CLUSTER5_BRT
3-0
LED Output 0 Brightness Control Mapping
0h = DISP_BRT/PWM
1h = CLUSTER1_BRT
2h = CLUSTER3_BRT
3h = CLUSTER3_BRT
4h = CLUSTER4_BRT
5h = CLUSTER5_BRT
8.6.1.4 GROUPING2 Register (Offset = 32h) [reset = 0h]
GROUPING2 is shown in Figure 37 and described in Table 17.
Return to Summary Table.
Figure 37. GROUPING2 Register
15
7
14
6
13
5
12
4
11
3
10
2
9
1
8
0
RESERVED
R/W-0h
LED5_GROUP
R/W-0h
LED4_GROUP
R/W-0h
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Table 17. GROUPING2 Register Field Descriptions
Bit
Field
Type
Reset
Description
15-8
RESERVED
R/W
0h
These bits are reserved.
7-4
LED5_GROUP
R/W
0h
LED Output 5 Brightness Control Mapping
0h = DISP_BRT/PWM
1h = CLUSTER1_BRT
2h = CLUSTER3_BRT
3h = CLUSTER3_BRT
4h = CLUSTER4_BRT
5h = CLUSTER5_BRT
3-0
LED4_GROUP
R/W
0h
LED Output 4 Brightness Control Mapping
0h = DISP_BRT/PWM
1h = CLUSTER1_BRT
2h = CLUSTER3_BRT
3h = CLUSTER3_BRT
4h = CLUSTER4_BRT
5h = CLUSTER5_BRT
8.6.1.5 USER_CONFIG1 Register (Offset = 40h) [reset = 8B0h]
USER_CONFIG1 is shown in Figure 38 and described in Table 18.
Return to Summary Table.
Figure 38. USER_CONFIG1 Register
15
7
14
13
5
12
11
10
2
9
8
DITHER_SELECT
RESERVED
TEMP_MON_E
N
RESERVED
R/W-0h
R/W-2h
3
R/W-0h
1
R/W-0h
0
6
4
SLOPE_SELECT
ADV_SLOPE_
ENABLE
RESERVED
DIMMING_MODE
R/W-5h
R/W-1h
R/W-0h
R/W-0h
Table 18. USER_CONFIG1 Register Field Descriptions
Bit
Field
Type
Reset
Description
15-13
DITHER_SELECT
R/W
0h
0h = Dither Disabled
1h = 1-bit Dither
2h = 2-bit Dither
3h = 3-bit Dither
4h = 4-bit Dither
5h = 5-bit Dither
6h = Unused
7h = Unused
12-10
9
RESERVED
R/W
R/W
2h
0h
These bits are reserved.
TEMP_MON_EN
0h = Temperature Monitor Disabled
1h = Temperature Monitor Enabled
8
RESERVED
R/W
0h
This bit is reserved.
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Table 18. USER_CONFIG1 Register Field Descriptions (continued)
Bit
Field
Type
Reset
Description
7-5
SLOPE_SELECT
R/W
5h
0h = 0ms
1h = 1ms
2h = 2ms
3h = 50ms
4h = 100ms
5h = 200ms
6h = 300ms
7h = 500ms Times are for linear slope mode. Advanced sloper will
increase durations while adding additional smoothing to brightness
transitions. 1ms and 2ms sloper times are intended to be used only
in linear mode. 50ms to 500ms sloper durations may be used with or
without advanced sloper function.
4
ADV_SLOPE_ENABLE
R/W
1h
0h = Linear Sloping
1h = Advanced Sloping
3-2
1-0
RESERVED
R/W
R/W
0h
0h
These bits are reserved.
DIMMING_MODE
LED Output Dimming Mode
0h = PWM Mode
1h = 12.5% Hybrid Mode
2h = Unused
3h = 12-bit Constant Current Mode
8.6.1.6 USER_CONFIG2 Register (Offset = 42h) [reset = 0h]
USER_CONFIG2 is shown in Figure 39 and described in Table 19.
Return to Summary Table.
Figure 39. USER_CONFIG2 Register
15
14
6
13
5
12
11
10
2
9
1
8
0
EN_MIN_PWM
_LIMIT
RESERVED
R/W-0h
7
R/W-0h
3
4
RESERVED
R/W-0h
Table 19. USER_CONFIG2 Register Field Descriptions
Bit
Field
EN_MIN_PWM_LIMIT
Type
Reset
Description
15
R/W
0h
Allows PWM pulses to be dithered to reduce lower minimum
brightness.
When enabled brightness levels that map to less than 200ns pulse
width will cause pulses to be skipped.
0h = Disabled
1h = Enabled
14-0
RESERVED
R/W
0h
These bits are reserved.
8.6.1.7 INTERRUPT_ENABLE_3 Register (Offset = 4Eh) [reset = 200Ah]
INTERRUPT_ENABLE_3 is shown in Figure 40 and described in Table 20.
Return to Summary Table.
50
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Figure 40. INTERRUPT_ENABLE_3 Register
15
14
13
VINOCP_INT_EN
R/W-2h
12
11
CPCAP_INT_EN
R/W-0h
10
9
1
8
0
BSTSYNC_INT_EN
R/W-0h
CP_INT_EN
R/W-0h
7
6
5
4
3
2
FSET_INT_EN
R/W-0h
INVSTRING_INT_EN
R/W-0h
VINOVP_INT_EN
R/W-2h
VINUVP_INT_EN
R/W-2h
Table 20. INTERRUPT_ENABLE_3 Register Field Descriptions
Bit
Field
Type
Reset
Description
15-14
13-12
11-10
9-8
BSTSYNC_INT_EN
VINOCP_INT_EN
CPCAP_INT_EN
CP_INT_EN
R/W
0h
Missing Boost Sync Interrupt Enable
Read:
0h = Interrupt is currently disabled
2h = Interrupt is currently enabled
Write:
1h = Disable Interrupt
3h = Enable Interrupt
R/W
R/W
R/W
R/W
R/W
2h
0h
0h
0h
0h
VIN Over-Current Interrupt Enable
Read:
0h = Interrupt is currently disabled
2h = Interrupt is currently enabled
Write:
1h = Disable Interrupt
3h = Enable Interrupt
Charge Pump Cap Missing Interrupt Enable
Read:
0h = Interrupt is currently disabled
2h = Interrupt is currently enabled
Write:
1h = Disable Interrupt
3h = Enable Interrupt
Charge Pump Interrupt Enable
Read:
0h = Interrupt is currently disabled
2h = Interrupt is currently enabled
Write:
1h = Disable Interrupt
3h = Enable Interrupt
7-6
FSET_INT_EN
Missing FSET Resistor Interrupt Enable
Read:
0h = Interrupt is currently disabled
2h = Interrupt is currently enabled
Write:
1h = Disable Interrupt
3h = Enable Interrupt
5-4
INVSTRING_INT_EN
Invalid LED String Configuration Interrupt Enable
Read:
0h = Interrupt is currently disabled
2h = Interrupt is currently enabled
Write:
1h = Disable Interrupt
3h = Enable Interrupt
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Table 20. INTERRUPT_ENABLE_3 Register Field Descriptions (continued)
Bit
Field
Type
Reset
Description
3-2
VINOVP_INT_EN
R/W
2h
VIN Over-Voltage Interrupt Enable
Read:
0h = Interrupt is currently disabled
2h = Interrupt is currently enabled
Write:
1h = Disable Interrupt
3h = Enable Interrupt
1-0
VINUVP_INT_EN
R/W
2h
VIN Under-Voltage Interrupt Enable
Read:
0h = Interrupt is currently disabled
2h = Interrupt is currently enabled
Write:
1h = Disable Interrupt
3h = Enable Interrupt
8.6.1.8 INTERRUPT_ENABLE_1 Register (Offset = 50h) [reset = A02Ah]
INTERRUPT_ENABLE_1 is shown in Figure 41 and described in Table 21.
Return to Summary Table.
Figure 41. INTERRUPT_ENABLE_1 Register
15
GLOBAL_INT_EN
R/W-2h
14
13
12
11
TEMP_INT_EN
R/W-0h
10
9
1
8
BSTOVPH_INT_EN
R/W-2h
RESERVED
R/W-0h
7
6
5
4
3
2
0
BSTOVPL_INT_EN
R/W-0h
BSTOCP_INT_EN
R/W-2h
VDDUVLO_INT_EN
R/W-2h
TSD_INT_EN
R/W-2h
Table 21. INTERRUPT_ENABLE_1 Register Field Descriptions
Bit
Field
Type
Reset
Description
15-14
13-12
11-10
9-8
GLOBAL_INT_EN
R/W
2h
Global Interrupt Enable
Read:
0h = Interrupt is currently disabled
2h = Interrupt is currently enabled
Write:
1h = Disable Interrupt
3h = Enable Interrupt
BSTOVPH_INT_EN
TEMP_INT_EN
RESERVED
R/W
R/W
R/W
2h
0h
0h
Boost OVP High Interrupt Enable
Read:
0h = Interrupt is currently disabled
2h = Interrupt is currently enabled
Write:
1h = Disable Interrupt
3h = Enable Interrupt
Temperature Interrupt Enable
Read:
0h = Interrupt is currently disabled
2h = Interrupt is currently enabled
Write:
1h = Disable Interrupt
3h = Enable Interrupt
These bits are reserved.
52
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ZHCSGN5B –MARCH 2017–REVISED JULY 2018
Table 21. INTERRUPT_ENABLE_1 Register Field Descriptions (continued)
Bit
Field
Type
Reset
Description
7-6
BSTOVPL_INT_EN
R/W
0h
Boost OVP Low Interrupt Enable
Read:
0h = Interrupt is currently disabled
2h = Interrupt is currently enabled
Write:
1h = Disable Interrupt
3h = Enable Interrupt
5-4
3-2
1-0
BSTOCP_INT_EN
VDDUVLO_INT_EN
TSD_INT_EN
R/W
R/W
R/W
2h
2h
2h
Boost Over-Current Interrupt Enable
Read:
0h = Interrupt is currently disabled
2h = Interrupt is currently enabled
Write:
1h = Disable Interrupt
3h = Enable Interrupt
VDD UVLO Interrupt Enable
Read:
0h = Interrupt is currently disabled
2h = Interrupt is currently enabled
Write:
1h = Disable Interrupt
3h = Enable Interrupt
Thermal Shutdown Interrupt Enable
Read:
0h = Interrupt is currently disabled
2h = Interrupt is currently enabled
Write:
1h = Disable Interrupt
3h = Enable Interrupt
8.6.1.9 INTERRUPT_ENABLE_2 Register (Offset = 52h) [reset = 80h]
INTERRUPT_ENABLE_2 is shown in Figure 42 and described in Table 22.
Return to Summary Table.
Figure 42. INTERRUPT_ENABLE_2 Register
15
7
14
6
13
5
12
4
11
3
10
9
1
8
0
RESERVED
R/W-0h
2
LED_INT_EN
R/W-2h
RESERVED
R/W-0h
Table 22. INTERRUPT_ENABLE_2 Register Field Descriptions
Bit
Field
Type
Reset
Description
15-8
7-6
RESERVED
R/W
0h
These bits are reserved.
LED_INT_EN
R/W
2h
LED Open / Short Interrupt Enable
Read:
0h = Interrupt is currently disabled
2h = Interrupt is currently enabled
Write:
1h = Disable Interrupt
3h = Enable Interrupt
5-0
RESERVED
R/W
0h
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8.6.1.10 INTERRUPT_STATUS_1 Register (Offset = 54h) [reset = 0h]
INTERRUPT_STATUS_1 is shown in Figure 43 and described in Table 23.
Return to Summary Table.
Figure 43. INTERRUPT_STATUS_1 Register
15
14
13
12
11
10
9
1
8
BSTOVPH_ST BSTOVPH_CL TEMPHIGH_ST TEMPHIGH_CL TEMPLOW_ST TEMPLOW_CL
RESERVED
R/W-0h
ATUS
EAR
ATUS
EAR
ATUS
EAR
R/W-0h
R/W-0h
R/W-0h
R/W-0h
R/W-0h
R/W-0h
7
6
5
4
3
2
0
BSTOVPL_STA BSTOVPL_CLE BSTOCP_STA BSTOCP_CLE VDDUVLO_ST VDDUVLO_CL TSD_STATUS
TSD_CLEAR
TUS
AR
TUS
AR
ATUS
EAR
R/W-0h
R/W-0h
R/W-0h
R/W-0h
R/W-0h
R/W-0h
R/W-0h
R/W-0h
Table 23. INTERRUPT_STATUS_1 Register Field Descriptions
Bit
Field
Type
Reset
Description
15
BSTOVPH_STATUS
R/W
0h
Boost OVP High Status
0h = No Fault
1h = Fault
14
13
BSTOVPH_CLEAR
R/W
R/W
0h
0h
Boost OVP High Fault Clear
Write "1" to both Status bit and Clear bit at same time to clear
interrupt register status and interrupt pin status.
TEMPHIGH_STATUS
Temperature High Status
0h = No Fault
1h = Fault
12
11
TEMPHIGH_CLEAR
TEMPLOW_STATUS
R/W
R/W
0h
0h
Temperature High Fault Clear
Write "1" to both Status bit and Clear bit at same time to clear
interrupt register status and interrupt pin status.
Temperature Low Status
0h = No Fault
1h = Fault
10
TEMPLOW_CLEAR
R/W
0h
Temperature Low Fault Clear
Write "1" to both Status bit and Clear bit at same time to clear
interrupt register status and interrupt pin status.
9-8
7
RESERVED
R/W
R/W
0h
0h
These bits are reserved.
BSTOVPL_STATUS
Boost OVP Low Status
0h = No Fault
1h = Fault
6
5
BSTOVPL_CLEAR
BSTOCP_STATUS
R/W
R/W
0h
0h
Boost OVP Low Fault Clear
Write "1" to both Status bit and Clear bit at same time to clear
interrupt register status and interrupt pin status.
Boost Over-Current Status
0h = No Fault
1h = Fault
4
3
BSTOCP_CLEAR
R/W
R/W
0h
0h
Boost Over-Current Fault Clear
Write "1" to both Status bit and Clear bit at same time to clear
interrupt register status and interrupt pin status.
VDDUVLO_STATUS
VDD UVLO Status
0h = No Fault
1h = Fault
54
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ZHCSGN5B –MARCH 2017–REVISED JULY 2018
Table 23. INTERRUPT_STATUS_1 Register Field Descriptions (continued)
Bit
Field
Type
Reset
Description
2
VDDUVLO_CLEAR
R/W
0h
VDD UVLO Fault Clear
Write "1" to both Status bit and Clear bit at same time to clear
interrupt register status and interrupt pin status.
1
0
TSD_STATUS
TSD_CLEAR
R/W
R/W
0h
0h
Thermal Shutdown Status
0h = No Fault
1h = Fault
Thermal Shutdown Fault Clear
Write "1" to both Status bit and Clear bit at same time to clear
interrupt register status and interrupt pin status.
8.6.1.11 INTERRUPT_STATUS_2 Register (Offset = 56h) [reset = 0h]
INTERRUPT_STATUS_2 is shown in Figure 44 and described in Table 24.
Return to Summary Table.
Figure 44. INTERRUPT_STATUS_2 Register
15
14
13
12
11
10
9
8
LED5_FAULT
R/W-0h
LED4_FAULT
R/W-0h
LED3_FAULT
R/W-0h
LED2_FAULT
R/W-0h
LED1_FAULT
R/W-0h
LED0_FAULT
R/W-0h
OPEN_LED
R/W-0h
SHORT_LED
R/W-0h
7
6
5
4
3
2
1
0
LED_STATUS
R/W-0h
LED_CLEAR
R/W-0h
RESERVED
R/W-0h
Table 24. INTERRUPT_STATUS_2 Register Field Descriptions
Bit
Field
Type
Reset
Description
15
LED5_FAULT
LED4_FAULT
LED3_FAULT
LED2_FAULT
LED1_FAULT
LED0_FAULT
R/W
0h
LED5 Status
0h = No Fault
1h = Fault
Status is cleared with LED_STATUS bit
14
13
12
11
10
R/W
R/W
R/W
R/W
R/W
0h
0h
0h
0h
0h
LED4 Status
0h = No Fault
1h = Fault
Status is cleared with LED_STATUS bit
LED3 Status
0h = No Fault
1h = Fault
Status is cleared with LED_STATUS bit
LED2 Status
0h = No Fault
1h = Fault
Status is cleared with LED_STATUS bit
LED1 Status
0h = No Fault
1h = Fault
Status is cleared with LED_STATUS bit
LED0 Status
0h = No Fault
1h = Fault
Status is cleared with LED_STATUS bit
Copyright © 2017–2018, Texas Instruments Incorporated
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Table 24. INTERRUPT_STATUS_2 Register Field Descriptions (continued)
Bit
Field
Type
Reset
Description
9
OPEN_LED
R/W
0h
LED Open Status
0h = No Fault
1h = Fault
Status is cleared with LED_STATUS bit
8
7
SHORT_LED
LED_STATUS
R/W
R/W
0h
0h
LED Short Status
0h = No Fault
1h = Fault
Status is cleared with LED_STATUS bit
LED Open / Short Fault Status
0h = No Fault
1h = Fault
6
LED_CLEAR
RESERVED
R/W
R/W
0h
0h
LED Open / Short Fault Clear
Write "1" to both Status bit and Clear bit at same time to clear
interrupt register status and interrupt pin status.
5-0
These bits are reserved.
8.6.1.12 INTERRUPT_STATUS_3 Register (Offset = 58h) [reset = 0h]
INTERRUPT_STATUS_3 is shown in Figure 45 and described in Table 25.
Return to Summary Table.
Figure 45. INTERRUPT_STATUS_3 Register
15
14
13
12
11
10
9
8
BSTSYNC_ST BSTSYNC_CL VINOCP_STAT VINOCP_CLEA CPCAP_STAT CPCAP_CLEA
CP_STATUS
CP_CLEAR
ATUS
EAR
US
R
US
R
R/W-0h
R/W-0h
R/W-0h
R/W-0h
R/W-0h
R/W-0h
R/W-0h
1
R/W-0h
0
7
6
5
4
3
2
FSET_STATUS FSET_CLEAR INVSTRING_S INVSTRING_C VINOVP_STAT VINOVP_CLEA VINUVP_STAT VINUVP_CLEA
TATUS
LEAR
US
R
US
R
R/W-0h
R/W-0h
R/W-0h
R/W-0h
R/W-0h
R/W-0h
R/W-0h
R/W-0h
Table 25. INTERRUPT_STATUS_3 Register Field Descriptions
Bit
Field
Type
Reset
Description
15
BSTSYNC_STATUS
R/W
0h
Missing Boost Sync Fault Status
0h = No Fault
1h = Fault
14
13
BSTSYNC_CLEAR
VINOCP_STATUS
R/W
R/W
0h
0h
Missing Boost Sync Fault Clear
Write "1" to both Status bit and Clear bit at same time to clear
interrupt register status and interrupt pin status.
VIN Over-Current Fault Status
0h = No Fault
1h = Fault
12
11
VINOCP_CLEAR
CPCAP_STATUS
R/W
R/W
0h
0h
VIN Over-Current Fault Clear
Write "1" to both Status bit and Clear bit at same time to clear
interrupt register status and interrupt pin status.
Missing Charge Pump Capacitor Fault Status
0h = No Fault
1h = Fault
56
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ZHCSGN5B –MARCH 2017–REVISED JULY 2018
Table 25. INTERRUPT_STATUS_3 Register Field Descriptions (continued)
Bit
Field
Type
Reset
Description
10
CPCAP_CLEAR
R/W
0h
Missing Charge Pump Capacitor Fault Clear
Write "1" to both Status bit and Clear bit at same time to clear
interrupt register status and interrupt pin status.
9
CP_STATUS
R/W
0h
Charge Pump Fault Status
0h = No Fault
1h = Fault
8
7
CP_CLEAR
R/W
R/W
0h
0h
Charge Pump Fault Fault Clear
Write "1" to both Status bit and Clear bit at same time to clear
interrupt register status and interrupt pin status.
FSET_STATUS
Missing Boost / PWM FSET Resistor Fault Status
0h = No Fault
1h = Fault
6
5
FSET_CLEAR
R/W
R/W
0h
0h
Missing Boost / PWM FSET Resistor Fault Clear
Write "1" to both Status bit and Clear bit at same time to clear
interrupt register status and interrupt pin status.
INVSTRING_STATUS
Invalid LED String Configuration Fault Status
0h = No Fault
1h = Fault
4
3
INVSTRING_CLEAR
VINOVP_STATUS
R/W
R/W
0h
0h
Invalid LED String Configuration Fault Clear
Write "1" to both Status bit and Clear bit at same time to clear
interrupt register status and interrupt pin status.
VIN Over-Voltage Fault Status
0h = No Fault
1h = Fault
2
1
VINOVP_CLEAR
VINUVP_STATUS
R/W
R/W
0h
0h
VIN Over-Voltage Fault Clear
Write "1" to both Status bit and Clear bit at same time to clear
interrupt register status and interrupt pin status.
VIN Under-Voltage Fault Status
0h = No Fault
1h = Fault
0
VINUVP_CLEAR
R/W
0h
VIN Under-Voltage Fault Clear
Write "1" to both Status bit and Clear bit at same time to clear
interrupt register status and interrupt pin status.
8.6.1.13 JUNCTION_TEMPERATURE Register (Offset = E8h) [reset = 100h]
JUNCTION_TEMPERATURE is shown in Figure 46 and described in Table 26.
Return to Summary Table.
Figure 46. JUNCTION_TEMPERATURE Register
15
7
14
6
13
12
11
10
9
1
8
RESERVED
JUNCTION_TE
MPERATURE
R-0h
4
R-100h
0
5
3
2
JUNCTION_TEMPERATURE
R-100h
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Table 26. JUNCTION_TEMPERATURE Register Field Descriptions
Bit
Field
Type
Reset
Description
15-9
RESERVED
R
0h
These bits are reserved.
8-0
JUNCTION_TEMPERATU
RE
R
100h
Junction Temperature ADC Measurement
2's complement number.
000h - 0FFh = 0 °C to 255 °C
100h - 1FFh = –256 °C to –1 °C
8.6.1.14 TEMPERATURE_LIMIT_HIGH Register (Offset = ECh) [reset = 7Dh]
TEMPERATURE_LIMIT_HIGH is shown in Figure 47 and described in Table 27.
Return to Summary Table.
Figure 47. TEMPERATURE_LIMIT_HIGH Register
15
7
14
6
13
12
11
10
9
1
8
RESERVED
TEMPERATUR
E_LIMIT_HIGH
R-0h
4
R/W-7Dh
0
5
3
2
TEMPERATURE_LIMIT_HIGH
R/W-7Dh
Table 27. TEMPERATURE_LIMIT_HIGH Register Field Descriptions
Bit
Field
Type
Reset
Description
15-9
8-0
RESERVED
R
0h
These bits are reserved.
TEMPERATURE_LIMIT_ R/W
HIGH
7Dh
High Limit for Junction Temperature Monitor
2's complement number.
000h - 0FFh = 0 °C to 255 °C
100h - 1FFh = –256 °C to –1 °C
8.6.1.15 TEMPERATURE_LIMIT_LOW Register (Offset = EEh) [reset = 69h]
TEMPERATURE_LIMIT_LOW is shown in Figure 48 and described in Table 28.
Return to Summary Table.
Figure 48. TEMPERATURE_LIMIT_LOW Register
15
7
14
6
13
12
11
10
9
1
8
RESERVED
TEMPERATUR
E_LIMIT_LOW
R-0h
4
R/W-69h
0
5
3
2
TEMPERATURE_LIMIT_LOW
R/W-69h
Table 28. TEMPERATURE_LIMIT_LOW Register Field Descriptions
Bit
Field
Type
Reset
Description
15-9
8-0
RESERVED
R
0h
These bits are reserved.
TEMPERATURE_LIMIT_L R/W
OW
69h
Low Limit for Junction Temperature Monitor
2's complement number.
000h - 0FFh = 0 °C to 255 °C
100h - 1FFh = –256 °C to –1 °C
58
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ZHCSGN5B –MARCH 2017–REVISED JULY 2018
8.6.1.16 CLUSTER1_BRT Register (Offset = 13Ch) [reset = FFFFh]
CLUSTER1_BRT is shown in Figure 49 and described in Table 29.
Return to Summary Table.
Figure 49. CLUSTER1_BRT Register
15
14
13
12
11
10
9
8
7
6
5
4
3
2
1
0
CLUSTER1_BRT
R/W-FFFFh
Table 29. CLUSTER1_BRT Register Field Descriptions
Bit
15-0
Field
CLUSTER1_BRT
Type
Reset
Description
R/W
FFFFh
CLUSTER1 Brightness Control.
This register controls LED output duty cycle for the LED outputs
assigned to LED GROUP 1.
This register is buffered, write LOAD_BRT_DB bit to update.
8.6.1.17 CLUSTER2_BRT Register (Offset = 148h) [reset = FFFFh]
CLUSTER2_BRT is shown in Figure 50 and described in Table 30.
Return to Summary Table.
Figure 50. CLUSTER2_BRT Register
15
14
13
12
11
10
9
8
7
6
5
4
3
2
1
0
CLUSTER2_BRT
R/W-FFFFh
Table 30. CLUSTER2_BRT Register Field Descriptions
Bit
15-0
Field
CLUSTER2_BRT
Type
Reset
Description
R/W
FFFFh
CLUSTER2 Brightness Control.
This register controls LED output duty cycle for the LED outputs
assigned to LED GROUP 2.
This register is buffered, write LOAD_BRT_DB bit to update.
8.6.1.18 CLUSTER3_BRT Register (Offset = 154h) [reset = FFFFh]
CLUSTER3_BRT is shown in Figure 51 and described in Table 31.
Return to Summary Table.
Figure 51. CLUSTER3_BRT Register
15
14
13
12
11
10
9
8
7
6
5
4
3
2
1
0
CLUSTER3_BRT
R/W-FFFFh
Table 31. CLUSTER3_BRT Register Field Descriptions
Bit
15-0
Field
CLUSTER3_BRT
Type
Reset
Description
R/W
FFFFh
CLUSTER3 Brightness Control.
This register controls LED output duty cycle for the LED outputs
assigned to LED GROUP 3.
This register is buffered, write LOAD_BRT_DB bit to update.
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8.6.1.19 CLUSTER4_BRT Register (Offset = 160h) [reset = FFFFh]
CLUSTER4_BRT is shown in Figure 52 and described in Table 32.
Return to Summary Table.
Figure 52. CLUSTER4_BRT Register
15
14
13
12
11
10
9
8
7
6
5
4
3
2
1
0
CLUSTER4_BRT
R/W-FFFFh
Table 32. CLUSTER4_BRT Register Field Descriptions
Bit
15-0
Field
CLUSTER4_BRT
Type
Reset
Description
R/W
FFFFh
CLUSTER4 Brightness Control.
This register controls LED output duty cycle for the LED outputs
assigned to LED GROUP 4.
This register is buffered, write LOAD_BRT_DB bit to update.
8.6.1.20 CLUSTER5_BRT Register (Offset = 16Ch) [reset = FFFFh]
CLUSTER5_BRT is shown in Figure 53 and described in Table 33.
Return to Summary Table.
Figure 53. CLUSTER5_BRT Register
15
14
13
12
11
10
9
8
7
6
5
4
3
2
1
0
CLUSTER5_BRT
R/W-FFFFh
Table 33. CLUSTER5_BRT Register Field Descriptions
Bit
15-0
Field
CLUSTER5_BRT
Type
Reset
Description
R/W
FFFFh
CLUSTER5 Brightness Control.
This register controls LED output duty cycle for the LED outputs
assigned to LED GROUP 5.
This register is buffered, write LOAD_BRT_DB bit to update.
8.6.1.21 BRT_DB_CONTROL Register (Offset = 178h) [reset = 0h]
BRT_DB_CONTROL is shown in Figure 54 and described in Table 34.
Return to Summary Table.
Figure 54. BRT_DB_CONTROL Register
15
7
14
6
13
5
12
11
3
10
9
1
8
0
RESERVED
R/W-0h
4
2
RESERVED
R/W-0h
LOAD_BRT_D
B
R/W-0h
Table 34. BRT_DB_CONTROL Register Field Descriptions
Bit
Field
Type
Reset
Description
15-1
0
RESERVED
R/W
0h
These bits are reserved.
LOAD_BRT_DB
R/W
0h
Write this bit to "1" to update CLUSTERx_BRT registers and
LEDx_CURRENT registers (those registers are buffered).
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8.6.1.22 LED0_CURRENT Register (Offset = 1C2h) [reset = FFFh]
LED0_CURRENT is shown in Figure 55 and described in Table 35.
Return to Summary Table.
Figure 55. LED0_CURRENT Register
15
14
6
13
12
11
10
9
8
0
LED0_SHORT_
DISABLE
RESERVED
LED0_CURRENT
R/W-0h
7
R/W-0h
5
R/W-FFFh
4
3
2
1
LED0_CURRENT
R/W-FFFh
Table 35. LED0_CURRENT Register Field Descriptions
Bit
Field
Type
Reset
Description
15
LED0_SHORT_DISABLE R/W
0h
Short Fault Disable for LED0
0h = Short LED Faults are detected for LED0 output
1h = Short LED Faults are not detected for LED0 output
14-12
11-0
RESERVED
R/W
R/W
0h
LED0_CURRENT
FFFh
Individual LED Current control for LED0 Output
8.6.1.23 LED1_CURRENT Register (Offset = 1C4h) [reset = FFFh]
LED1_CURRENT is shown in Figure 56 and described in Table 36.
Return to Summary Table.
Figure 56. LED1_CURRENT Register
15
14
6
13
12
11
10
9
8
0
LED1_SHORT_
DISABLE
RESERVED
LED1_CURRENT
R/W-0h
7
R/W-0h
5
R/W-FFFh
4
3
2
1
LED1_CURRENT
R/W-FFFh
Table 36. LED1_CURRENT Register Field Descriptions
Bit
Field
Type
Reset
Description
15
LED1_SHORT_DISABLE R/W
0h
Short Fault Disable for LED1
0h = Short LED Faults are detected for LED1 output
1h = Short LED Faults are not detected for LED1 output
14-12
11-0
RESERVED
R/W
R/W
0h
LED1_CURRENT
FFFh
Individual LED Current control for LED1 Output
8.6.1.24 LED2_CURRENT Register (Offset = 1C6h) [reset = FFFh]
LED2_CURRENT is shown in Figure 57 and described in Table 37.
Return to Summary Table.
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Figure 57. LED2_CURRENT Register
15
14
6
13
12
11
10
9
8
LED2_SHORT_
DISABLE
RESERVED
LED2_CURRENT
R/W-0h
7
R/W-0h
5
R/W-FFFh
4
3
2
1
0
LED2_CURRENT
R/W-FFFh
Table 37. LED2_CURRENT Register Field Descriptions
Bit
Field
Type
Reset
Description
15
LED2_SHORT_DISABLE R/W
0h
Short Fault Disable for LED2
0h = Short LED Faults are detected for LED2 output
1h = Short LED Faults are not detected for LED2 output
14-12
11-0
RESERVED
R/W
R/W
0h
LED2_CURRENT
FFFh
Individual LED Current control for LED2 Output
8.6.1.25 LED3_CURRENT Register (Offset = 1C8h) [reset = FFFh]
LED3_CURRENT is shown in Figure 58 and described in Table 38.
Return to Summary Table.
Figure 58. LED3_CURRENT Register
15
14
6
13
12
11
10
9
8
0
LED3_SHORT_
DISABLE
RESERVED
LED3_CURRENT
R/W-0h
7
R/W-0h
5
R/W-FFFh
4
3
2
1
LED3_CURRENT
R/W-FFFh
Table 38. LED3_CURRENT Register Field Descriptions
Bit
Field
Type
Reset
Description
15
LED3_SHORT_DISABLE R/W
0h
Short Fault Disable for LED3
0h = Short LED Faults are detected for LED3 output
1h = Short LED Faults are not detected for LED3 output
14-12
11-0
RESERVED
R/W
R/W
0h
LED3_CURRENT
FFFh
Individual LED Current control for LED3 Output
8.6.1.26 LED4_CURRENT Register (Offset = 1CAh) [reset = FFFh]
LED4_CURRENT is shown in Figure 59 and described in Table 39.
Return to Summary Table.
Figure 59. LED4_CURRENT Register
15
14
6
13
12
11
10
9
8
0
LED4_SHORT_
DISABLE
RESERVED
LED4_CURRENT
R/W-0h
7
R/W-0h
5
R/W-FFFh
4
3
2
1
LED4_CURRENT
R/W-FFFh
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Table 39. LED4_CURRENT Register Field Descriptions
Bit
Field
Type
Reset
Description
15
LED4_SHORT_DISABLE R/W
0h
Short Fault Disable for LED4
0h = Short LED Faults are detected for LED4 output
1h = Short LED Faults are not detected for LED4 output
14-12
11-0
RESERVED
R/W
R/W
0h
LED4_CURRENT
FFFh
Individual LED Current control for LED4 Output
8.6.1.27 LED5_CURRENT Register (Offset = 1CCh) [reset = FFFh]
LED5_CURRENT is shown in Figure 60 and described in Table 40.
Return to Summary Table.
Figure 60. LED5_CURRENT Register
15
14
6
13
12
11
10
9
8
0
LED5_SHORT_
DISABLE
RESERVED
LED5_CURRENT
R/W-0h
7
R/W-0h
5
R/W-FFFh
4
3
2
1
LED5_CURRENT
R/W-FFFh
Table 40. LED5_CURRENT Register Field Descriptions
Bit
Field
Type
Reset
Description
15
LED5_SHORT_DISABLE R/W
0h
Short Fault Disable for LED5
0h = Short LED Faults are detected for LED5 output
1h = Short LED Faults are not detected for LED5 output
14-12
11-0
RESERVED
R/W
R/W
0h
LED5_CURRENT
FFFh
Individual LED Current control for LED5 Output
8.6.1.28 BOOST_CONTROL Register (Offset = 288h) [reset = 1C0h]
BOOST_CONTROL is shown in Figure 61 and described in Table 41.
Return to Summary Table.
Figure 61. BOOST_CONTROL Register
15
7
14
6
13
12
11
3
10
9
1
8
0
LED_EXT_SUPPLY
R/W-0h
RESERVED
R/W-1C0h
5
4
2
RESERVED
R/W-1C0h
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Table 41. BOOST_CONTROL Register Field Descriptions
Bit
Field
Type
Reset
Description
15-10
LED_EXT_SUPPLY
R/W
0h
Selects whether external LED voltage supply is used for a LED
output.
Bit 15 = LED5
Bit 14 = LED4
Bit 13 = LED3
Bit 12 = LED2
Bit 11 = LED1
Bit 10 = LED0
0h = LP8863 Boost Converter Supply is used
1h = External Supply is used.
9-0
RESERVED
R/W
1C0h
These bits are reserved.
8.6.1.29 SHORT_THRESH Register (Offset = 28Ah) [reset = 2882h]
SHORT_THRESH is shown in Figure 62 and described in Table 42.
Return to Summary Table.
Figure 62. SHORT_THRESH Register
15
7
14
6
13
5
12
4
11
3
10
SHORTED_LED_THRESHOLD
R/W-4h
9
1
8
RESERVED
R/W-2h
RESERVED
R/W-82h
2
0
RESERVED
R/W-82h
Table 42. SHORT_THRESH Register Field Descriptions
Bit
Field
RESERVED
Type
Reset
Description
15-12
11-9
R/W
2h
This bit is reserved.
SHORTED_LED_THRES R/W
HOLD
4h
Threshold for detecting Shorted LED Fault on LED outputs.
Fault is detected when LEDx pin voltage (referenced to ground)
exceeds selected threshold when LED driver is enabled.
0h = 2.6V
1h = 3.0V
2h = 3.4V
3h = 3.8V
4h = 4.2V
5h = 4.8V
6h = 5.2V
7h = 6.0V
8-0
RESERVED
R/W
82h
These bits are reserved.
8.6.1.30 FSM_DIAGNOSTICS Register (Offset = 2A4h) [reset = 0h]
FSM_DIAGNOSTICS is shown in Figure 63 and described in Table 43.
Return to Summary Table.
Figure 63. FSM_DIAGNOSTICS Register
15
14
13
12
11
10
9
8
RESERVED
R-0h
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7
6
5
4
3
2
1
0
RESERVED
R-0h
FSM_LIVE_STATUS
R-0h
Table 43. FSM_DIAGNOSTICS Register Field Descriptions
Bit
Field
Type
Reset
Description
15-5
RESERVED
R
0h
These bits are reserved.
4-0
FSM_LIVE_STATUS
R
0h
Current status of Device state machine.
1h = LDO_STARTUP
2h = EEPROM_READ
3h = STANDBY
4h - Ch = BOOST_START
Dh = NORMAL
Eh = DISCHARGE
Fh = SHUTDOWN
10h = FAULT_RECOVERY
11h = ALL_LED_FAULT
8.6.1.31 PWM_INPUT_DIAGNOSTICS Register (Offset = 2A6h) [reset = 0h]
PWM_INPUT_DIAGNOSTICS is shown in Figure 64 and described in Table 44.
Return to Summary Table.
Figure 64. PWM_INPUT_DIAGNOSTICS Register
15
14
13
12
11
10
9
8
7
6
5
4
3
2
1
0
PWM_INPUT_STATUS
R-0h
Table 44. PWM_INPUT_DIAGNOSTICS Register Field Descriptions
Bit
15-0
Field
PWM_INPUT_STATUS
Type
Reset
Description
16bit value for detected duty cycle of PWM input signal.
R
0h
8.6.1.32 PWM_OUTPUT_DIAGNOSTICS Register (Offset = 2A8h) [reset = 0h]
PWM_OUTPUT_DIAGNOSTICS is shown in Figure 65 and described in Table 45.
Return to Summary Table.
Figure 65. PWM_OUTPUT_DIAGNOSTICS Register
15
14
13
12
11
10
9
8
7
6
5
4
3
2
1
0
LED_PWM_STATUS
R-0h
Table 45. PWM_OUTPUT_DIAGNOSTICS Register Field Descriptions
Bit
15-0
Field
LED_PWM_STATUS
Type
Reset
Description
R
0h
16-bit PWM Duty Code that Brightness path is driving to LED0
output.
8.6.1.33 LED_CURR_DIAGNOSTICS Register (Offset = 2AAh) [reset = 0h]
LED_CURR_DIAGNOSTICS is shown in Figure 66 and described in Table 46.
Return to Summary Table.
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Figure 66. LED_CURR_DIAGNOSTICS Register
15
7
14
6
13
12
11
10
9
8
0
RESERVED
R-0h
LED_CURRENT_STATUS
R-0h
5
4
3
2
1
LED_CURRENT_STATUS
R-0h
Table 46. LED_CURR_DIAGNOSTICS Register Field Descriptions
Bit
Field
Type
Reset
Description
15-12
11-0
RESERVED
R
0h
These bits are reserved.
LED_CURRENT_STATU
S
R
0h
12-bit Current DAC Code that Brightness path is driving to LED0
output.
8.6.1.34 ADAPT_BOOST_DIAGNOSTICS Register (Offset = 2ACh) [reset = 0h]
ADAPT_BOOST_DIAGNOSTICS is shown in Figure 67 and described in Table 47.
Return to Summary Table.
Figure 67. ADAPT_BOOST_DIAGNOSTICS Register
15
7
14
6
13
12
11
10
2
9
8
0
RESERVED
R-0h
VBOOST_STATUS
R-0h
5
4
3
1
VBOOST_STATUS
R-0h
Table 47. ADAPT_BOOST_DIAGNOSTICS Register Field Descriptions
Bit
Field
Type
Reset
Description
15-11
10-0
RESERVED
R
0h
These bits are reserved.
VBOOST_STATUS
R
0h
11-bit Boost Voltage Code that Adaptive Voltage Control Loop is
sending to Analog Boost Block.
Boost Output Voltage =
((R_FB1/R_FB2)*1.2)+(R_FB1*18.75nA*VBOOST_STATUS)
8.6.1.35 AUTO_DETECT_DIAGNOSTICS Register (Offset = 2AEh) [reset = 0h]
AUTO_DETECT_DIAGNOSTICS is shown in Figure 68 and described in Table 48.
Return to Summary Table.
Figure 68. AUTO_DETECT_DIAGNOSTICS Register
15
14
13
12
11
10
9
1
8
RESERVED
AUTO_PWM_F
REQ_SEL
R-0h
R-0h
0
7
6
5
4
AUTO_BOOST_FREQ_SEL
R-0h
3
2
AUTO_PWM_FREQ_SEL
R-0h
AUTO_LED_STRING_CFG
R-0h
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Table 48. AUTO_DETECT_DIAGNOSTICS Register Field Descriptions
Bit
Field
Type
Reset
Description
15-9
RESERVED
R
0h
These bits are reserved.
8-6
5-3
2-0
AUTO_PWM_FREQ_SEL
R
R
R
0h
0h
0h
PWM Frequency Setting based on PWM_FSET resistor detection.
0h = 152Hz
1h = 305Hz
2h = 610 Hz
3h = 1.22kHz
4h = 2.44kHz
5h = 4.88kHz
6h = 9.77kHz
7h = 19.53kHz
AUTO_BOOST_FREQ_S
EL
Boost Frequency Setting based on BST_FSET resistor detection.
0h = 303kHz
1h = 400kHz
2h = 606kHz
3h = 800kHz
4h = 1MHz
5h = 1.25 MHz
6h = 1.67MHz
7h = 2.2MHz
AUTO_LED_STRING_CF
G
Detected LED string configuration.
0h = 6 separate strings
1h = 5 separate strings
2h = 4 separate strings
3h = 3 separate strings
4h = 2 separate strings
5h = outputs connected in groups of 2 to drive 3 strings
6h = outputs connected in groups of 3 to drive 2 strings
7h = all outputs connected together to drive one string
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9 Application and Implementation
注
Information in the following applications sections is not part of the TI component
specification, and TI does not warrant its accuracy or completeness. TI’s customers are
responsible for determining suitability of components for their purposes. Customers should
validate and test their design implementation to confirm system functionality.
9.1 Application Information
The LP8863-Q1 device is designed for automotive applications, and an input voltage VIN is intended to be
connected to the vehicle battery. Depending on the input voltage, the device may be used in either boost mode
or SEPIC mode. The device is internally powered from the VDD pin, and voltage must be in 2.7-V to 5.5-V range.
The device has flexible configurability through external components or by an SPI or I2C interface. If the VDD
voltage is not high enough to drive an external nMOSFET gate, an internal charge pump must be used to power
the gate driver (GD pin).
注
For applications where VIN voltage is below the output voltage, use a boost converter
topology. Maximum operating voltage for VIN is 48 V, and the boost converter can achieve
output voltage up to 47 V. Conversion ratio of 5.5 (full load) or 10 (half load) must be
taken into account. If VIN voltage is expected to be below or above output voltage, a
SEPIC converter can be implemented. The SEPIC converter can achieve maximum output
voltage up to 24 V, and maximum conversion ratio for SEPIC mode is 5.
9.2 Typical Applications
9.2.1 Full Feature Application for Display Backlight
图 69 shows a full application for the LP8863-Q1 device in a boost topology. It supports 6 LED strings in display
mode, each at 100 mA, with an automatic 60° phase shift. Brightness control register is used for LED dimming
method through I2C communication. The charge pump is enabled for a 400-kHz boost switching frequency with
spread spectrum.
68
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Typical Applications (接下页)
D1
Q2
L1
RISENSE
VIN
VOUT
COUT
RSD
CIN
CPUMP
RFB1
RFB2
CPUMP
CPUMP
Q1
GD
GD
ISNS
C1N
PGND
RSENSE
C2x
PGND
ISNSGND
C1P
VDD
FB
VDD
DISCHARGE
GND
CVDD
CLDO
VLDO
LED0
LED1
LED2
LED3
LP8863-Q1
VDDIO
IFSEL
HOST
EN
INT
SDO_PWM
SDI_SDA
SCLK_SCL
LED4
LED5
ISET
I2C
SS_ADDRSEL
BST_SYNC
RISET
PWM_FSET
BST_FSET
RPWM
VDDIO
RBST
Copyright © 2017, Texas Instruments Incorporated
图 69. Full Feature Application for Display Backlight
9.2.1.1 Design Requirements
This typical LED-driver application is designed to meet the parameters listed in 表 49:
表 49. LP8863-Q1 Full-Feature Design Parameters
DESIGN PARAMETER
VIN voltage range
VALUE
3 V to 20 V
VDD voltage
3.3 V
LED strings configuration
Charge pump
6 strings, 7 LEDs in series
Enabled
I2C
Brightness control
Output configuration
LED string current
Boost frequency
Inductor
LED0 to LED5 are in display mode (phase shift 60°)
100 mA
400 kHz
22 µH at 12-A saturation current
RISENSE
20 mΩ
Power-line FET
RSENSE
Enabled
20 mΩ
Input/Output capacitors
Spread spectrum
Discharge function
CIN and COUT: 2 × 33-µF electrolytic + 2 × 10-µF ceramic
Enabled
Enabled
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9.2.1.2 Detailed Design Procedure
9.2.1.2.1 Inductor Selection
There are a few things to consider when choosing an inductor: inductance, current rating, and DC resistance
(DCR). 表 50 shows recommended inductor values for each operating frequency. The LP8863-Q1 device
automatically sets internal boost compensation controls depending on the selected switching frequency.
表 50. Inductance Values for Boost Switching Frequencies
SW FREQUENCY (kHz)
INDUCTANCE (µH)
300
400
22
22
15
15
10
10
10
10
600
800
1000
1250
1667
2200
The current rating of inductor must be at least 25% higher than maximum boost switching current ISW(max), which
can be calculated with 公式 12. TI recommends a current rating of 12 A for most applications; use an inductor
with low DCR to achieve good efficiency. Efficiency varies with load condition, switching frequency, and
components, but 80% can be use as safe estimation. Power Stage Designer™ Tools can be used for the boost
calculation: http://www.ti.com/tool/powerstage-designer
IOUT(max)
DIL
2
ISW(max)
=
+
1- D
where
•
•
•
•
•
•
•
•
•
•
•
ΔIL = VIN(min) × D / ( ƒSW × L )
D = 1 – VIN(min) × η / VOUT
ISW(max): Maximum switching current
ΔIL: Inductor ripple current
IOUT(max): Maximum output current
D: Boost duty cycle
VIN(min): Minimum input voltage
ƒSW: Minimum switching frequency of the converter
L: Inductance
VOUT: Output voltage
η: Efficiency of boost converter
(12)
9.2.1.2.2 Output Capacitor Selection
Recommended voltage rating for output capacitors is 50% higher than maximum output voltage level — 100-V
voltage rating is recommended. Capacitance value determines voltage ripple and boost stability. The DC-bias
effect can reduce the effective capacitance significantly, by up to 80%, a consideration for capacitance value
selection. Effective capacitance must be at least 50 µF for full load/maximum conversion ratio applications and
must be used to achieve good phase and gain margin levels. TI recommends using two 33-µF Al-polymer
electrolytic capacitors and two 10-µF ceramic capacitors in parallel to reduce ripple, increase stability, and
reduce ESR effect.
9.2.1.2.3 Input Capacitor Selection
Recommended input capacitance is the same as output capacitance although input capacitors are not as critical
to boost operation. Input capacitance can be reduced but must ensure enough filtering for input power.
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9.2.1.2.4 Charge Pump Output Capacitor
TI recommends a ceramic capacitor with at least 16-V voltage rating for the output capacitor of the charge pump.
A 10-μF capacitor can be used for most applications.
9.2.1.2.5 Charge Pump Flying Capacitor
TI recommends a ceramic capacitor with at least 16-V voltage rating for the flying capacitor of the charge pump.
One 2.2-μF capacitor connecting C1P and C1N pins can be used for most applications.
9.2.1.2.6 Output Diode
A Schottky diode must be used for the boost output diode. Current rating must be at least 25% higher than the
maximum output current; TI recommends a 12-A current rating for most applications. Schottky diodes with a low
forward drop and fast switching speeds are ideal for increasing efficiency. At maximum current, the forward
voltage must be as low as possible; less than 0.5 V is recommended. Reverse breakdown voltage of the
Schottky diode must be significantly larger than the output voltage, 25% higher voltage rating is recommended.
Do not use ordinary rectifier diodes, because slow switching speeds and long recovery times cause efficiency
and load regulation to suffer.
9.2.1.2.7 Switching FET
Gate-drive voltage for the FET is VDD with charge pump bypassed, or about double VDD, if the charge pump is
enabled. Switching FET is a critical component for determining power efficiency of the boost converter. Several
aspects need to be considered when selecting switching FET such as voltage and current rating, RDSON, power
dissipation, thermal resistance and rise/fall times. An N type MOSFET with at least 25% higher voltage rating
than maximum output voltage must be used. Current rating of switching FET should be same or higher than
inductor rating. RDSON must be as low as possible, less than 20 mΩ is recommended. Thermal resistance (RθJA
)
must also be low to dissipate heat from power loss on switching FET. TI recommends typical rise/fall time values
less than 10 ns.
9.2.1.2.8 Boost Sense Resistor
The RSENSE resistor determines the boost overcurrent limit and is sensed every boost switching cycle. A high-
power 20-mΩ resistor can be used for sensing the boost SW current and setting maximum current limit at 10 A
(typical). RSENSE can be increased to lower this limit and can be calculated with 公式 13, but this should be done
carefully because it may also affect stability. Boost overcurrent limit must not be set below 4 A, therefore RSENSE
must not exceed 50 mΩ. Power rating can be calculated from the inductor current and sense resistor resistance
value.
200 mV
RSENSE
=
IBOOST _OCP
where
•
•
RSENSE: boost sense resistor (mΩ)
IBOOST_OCP: boost overcurrent limit
(13)
9.2.1.2.9 Power-Line FET
A power line FET can be used to disconnect input power from boost input to protect the LP8863-Q1 device and
boost components in case an overcurrent event occurs. A P type MOSFET is used for the power-line FET.
Voltage rating must be at least 25% higher than maximum input voltage level. Low RDSON is important to reduce
power loss on the FET — less than 20 mΩ is recommended. Current rating for the FET must be at least 25%
higher than input peak current. Gate-to-source voltage (VGS) for open transistor must be less than minimum input
voltage; use a 20-kΩ resistor between the pFET gate and source.
9.2.1.2.10 Input Current Sense Resistor
A high-power resistor can be used for sensing the boost input current. Overcurrent condition is detected when
the voltage across RISENSE reaches 220 mV. Typical 20 mΩ sense resistor is used to set 11-A input current limit.
Sense resistor value can be increased to lower overcurrent limit for application as needed. Power rating can be
calculated from the input current and resistance value.
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9.2.1.2.11 Feedback Resistor Divider
Feedback resistors RFB1 and RFB2 determine the maximum boost output level. Output voltage can be calculated
as in 公式 14:
≈
∆
«
’
VBG
VOUT_MAX
=
+ ISEL_MAX ì RFB1 + VBG
÷
RFB2
◊
where
•
•
•
VBG = 1.21 V
ISEL_MAX = 38.7 µA
RFB2 = 100 kΩ (recommended for boost mode)
(14)
9.2.1.2.12 Critical Components for Design
图 70 shows the critical part of circuitry: boost components, the LP8863-Q1 internal charge pump for gate-driver
powering, and powering/grounding of LP8863-Q1. Schematic example is shown in 图 70.
D1
Q2
L1
RISENSE
VIN
VOUT
COUT
RSD
CIN
CPUMP
RFB1
CPUMP
CPUMP
Q1
GD
GD
ISNS
C1N
PGND
RSENSE
RFB2
C2x
PGND
ISNSGND
C1P
VDD
FB
VDD
DISCHARGE
GND
CVDD
VLDO
LED0
LED1
LED2
LED3
CLDO
LP8863-Q1
VDDIO
IFSEL
HOST
EN
INT
SDO_PWM
SDI_SDA
SCLK_SCL
LED4
LED5
ISET
I2C
SS_ADDRSEL
BST_SYNC
RISET
PWM_FSET
BST_FSET
RPWM
VDDIO
RBST
Copyright © 2017, Texas Instruments Incorporated
图 70. Critical Components for Full Feature Design
72
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ZHCSGN5B –MARCH 2017–REVISED JULY 2018
表 51. Recommended Component Values for Full Feature Design Example
REFERENCE
DESCRIPTION
NOTE
DESIGNATOR
RISENSE
RSD
20 mΩ, 3 W
20 kΩ, 0.1 W
Input current sensing resistor
Power-line FET gate pullup resistor
Boost current sensing resistor
Bottom feedback divider resistor
Top feedback divider resistor
Boost frequency set resistor
Current set resistor for 100 mA maximum
Output PWM frequency set resistor
Charge-pump output capacitor
Flying capacitor
RSENSE
RFB2
20 mΩ, 3 W
100 kΩ, 0.1 W
RFB1
910 kΩ, 0.1 W
RBST
RISET
RPWM
CPUMP
C2X
4.77 kΩ, 0.1 W
31.2 kΩ, 0.1 W
42.2 kΩ, 0.1 W
10-µF, 16-V ceramic
2.2-µF, 25-V ceramic
CVDD
CLDO
CIN
4.7-µF + 0.1-µF, 10-V ceramic
4.7-µF + 0.1-µF, 10-V ceramic
2 × 33-µF, 63-V electrolytic + 2 × 10-µF, 100-V ceramic
2 × 33-µF, 63-V electrolytic + 2 × 10-µF, 100-V ceramic
22-μH saturation current 23 A
100 V, 10-A Schottky diode
60-V, 25-A nMOSFET
VDD bypass capacitor
VLDO bypass capacitor
Boost input capacitor
COUT
L1
Boost output capacitor
Boost inductor
D1
Boost Schottky diode
Q1
Boost nMOSFET
Q2
60-V, 30-A pMOSFET
Power-line FET
9.2.1.3 Application Curves
FLED_PWM = 300 Hz
Phase Shift 60°
6 Strings
ƒSW = 400 kHz
100 mA/String
CIN = COUT = 2 × 33 μF (electrolytic) + 2 × 10 μF (ceramic)
图 71. LED String Currents Showing Phase Shift PWM
图 72. Typical Start-Up
Operation
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9.2.2 Application With Basic/Minimal Operation
The LP8863-Q1 needs only a few external components for basic functionality if material cost and PCB area for a
solution need to be minimized. In this example LP8863-Q1 is configured with external components and no I2C or
SPI communication. The power-line FET is removed, as is input current sensing. Internal charge pump is not
used, and all external synchronization functions and special features are disabled. Only 5 LED strings are
enabled.
D1
L1
VIN
VOUT
COUT
CIN
CPUMP
RFB1
CPUMP
CPUMP
Q1
GD
GD
ISNS
C1N
PGND
RSENSE
RFB2
PGND
ISNSGND
C1P
RFB3
VDD
FB
VDD
DISCHARGE
CVDD
GND
VLDO
LED0
LED1
LED2
LED3
LED4
CLDO
LP8863-Q1
VDDIO
IFSEL
EN
INT
SDO_PWM
SDI_SDA
SCLK_SCL
LED5
ISET
SS_ADDRSEL
BST_SYNC
RISET
PWM_FSET
BST_FSET
RPWM
RBST
Copyright © 2017, Texas Instruments Incorporated
图 73. Minimal Solution/Minimum Components Application
74
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ZHCSGN5B –MARCH 2017–REVISED JULY 2018
9.2.2.1 Design Requirements
This typical LED-driver application is designed to meet the parameters listed in 表 52:
表 52. LP8863-Q1 Minimal Solution Design Parameters
DESIGN PARAMETER
VIN voltage range
VALUE
5 V to 30 V
VDD voltage
5 V (note: 5 V required when charge pump disabled.)
5 strings, 10 LEDs in series
LED strings configuration
RFB1 = 100 kΩ, RFB2 = 6 kΩ , RFB3 = 27 kΩ (maximum output
voltage set to 43.5 V)
3-resistor feedback network
Charge pump
Disabled
Brightness control
PWM input
LED0 to LED4 are in display mode (phase shift 72°); LED5 is
not used (GND)
Output configuration
LED string current
Boost frequency
Inductor
150 mA
300 kHz
22 µH at 12-A saturation current
Power-line FET
RSENSE
Disabled
20 mΩ
Power-line FET
RSENSE
Enabled
20 mΩ
Input/Output capacitors
Spread spectrum
Discharge function
CIN and COUT: 2 × 33-µF electrolytic + 2 × 10-µF ceramic
Disabled
Disabled
9.2.2.2 Detailed Design Procedure
See Detailed Design Procedure
9.2.2.3 Application Curves
See Application Curves
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9.2.3 SEPIC Mode Application
When LED string voltage can be above and below the input voltage level, use the SEPIC configuration. In SEPIC
mode, the SW pin detects a maximum voltage equal to the sum of the input and output voltages, a consideration
when selecting components. This fact limits the maximum output voltage to 24 V. External frequency can be
used to synchronize boost or SEPIC switching frequency through the BST_SYNC pin.
CS2
RS
D1
Q2
L1
RISENSE
VIN
VOUT
COUT
RFB1
RSD
CIN
CS1
L2
CPUMP
CPUMP
CPUMP
Q1
GD
GD
ISNS
C1N
PGND
RSENSE
RFB2
C2x
PGND
ISNSGND
C1P
VDD
FB
VDD
DISCHARGE
GND
CVDD
VLDO
LED0
LED1
LED2
LED3
CLDO
LP8863-Q1
VDDIO
IFSEL
HOST
EN
INT
SDO_PWM
SDI_SDA
LED4
LED5
ISET
SCLK_SCL
SPI
SS_ADDRSEL
RISET
PWM_FSET
BST_FSET
BST_SYNC
RPWM
RBST
Copyright © 2017, Texas Instruments Incorporated
图 74. SEPIC Mode with Three LEDs in Series
76
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ZHCSGN5B –MARCH 2017–REVISED JULY 2018
9.2.3.1 Design Requirements
This typical LED-driver application is designed to meet the parameters listed in 表 53:
表 53. LP8863-Q1 SEPIC Mode Design Parameters
DESIGN PARAMETER
VIN voltage range
VALUE
3 V to 48 V
VDD voltage
3.3 V
LED strings configuration
Charge pump
6 strings, 3 LEDs in series
Enabled
SPI
Brightness control
Output configuration
LED string current
LED0 to LED5 are in display mode (phase shift 60°)
150 mA
2.2 MHz (Note: BST_SYNC frequency must be 0.2 to 0.5%
higher than frequency set by BST_FSET resistor.)
BST_SYNC external signal frequency
BST_FSET resistor
Inductor
42.2 kΩ (sets boost frequency to 1.6 MHz)
10 µH at 12-A saturation current
RISENSE
20 mΩ
Power-line FET
RSENSE
Enabled
20 mΩ
Input/Output capacitors
Spread spectrum
Discharge function
Boost synchronization
CIN and COUT: 2 × 33-µF electrolytic + 2 × 10-µF ceramic
Disabled
Enabled
Enabled
.
9.2.3.2 Detailed Design Procedure
9.2.3.2.1 Inductor Selection
Inductance for both inductors can be selected from 表 54, depending on operating frequency for the application.
Current rating is recommended to be at least 25% higher than maximum inductor peak current. Peak-to-peak
ripple current can be estimated to be approximately 40% of the maximum input current and and inductor peak
current can be calculated with 公式 15, 公式 16, and 公式 17:
表 54. Inductance Values for SEPIC Switching
Frequencies
SW FREQUENCY (kHz)
INDUCTANCE (µH)
300
400
15
15
600
10
800
10
1000
1250
1667
2200
6.8
6.8
4.7
4.7
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VOUT + VD
40%
2
≈
’
IL1(peak) = IOUT
ì
ì
1+
∆
«
÷
◊
V
IN(min)
where
•
•
•
•
•
IL1(peak): Peak current for inductor 1
IOUT: Maximum output current
VOUT: Output voltage
VD: Diode forward voltage drop
VIN(min): Minimum input voltage
(15)
(16)
40%
2
≈
’
IL2(peak) = IOUT
ì
1+
∆
«
÷
◊
where
•
•
IL2(peak): Peak current for inductor 2
IOUT: Maximum output current
VOUT
DIL = I ì 40% = IOUT
ì
ì 40%
IN
V
IN(min)
where
•
•
•
•
ΔIL: Inductor ripple current
IIN: Input current
VOUT: Output voltage
VIN(min): Minimum input voltage
(17)
9.2.3.2.2 Coupling Capacitor Selection
The coupling capacitors Cs isolate the input from the output and provide protection against a shorted load. The
selection of SEPIC capacitors, Cs, depends mostly on the RMS current, which can be calculated with 公式 18.
The capacitors must be rated for a large RMS current relative to the output power; TI recommends at least 25%
higher rating for IRMS. When using uncoupled inductors, use one 10-µF ceramic capacitor in parallel with one 33-
µF electrolytic capacitor and series 2-Ω resistor. If coupled inductors are used, then use only one 10-µF ceramic
capacitor.
VOUT + VD
ICs(rms) = IOUT
ì
V
IN(min)
where
•
•
•
•
•
ICs(rms): RMS current of Cs capacitor
IOUT: Output current
VOUT: Output voltage
VD: Diode forward voltage drop
VIN(min): Minimum input voltage
(18)
9.2.3.2.3 Output Capacitor Selection
See Detailed Design Procedure
9.2.3.2.4 Input Capacitor Selection
See Detailed Design Procedure
9.2.3.2.5 Charge Pump Output Capacitor
See Detailed Design Procedure
9.2.3.2.6 Charge Pump Flying Capacitor
See Detailed Design Procedure
78
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ZHCSGN5B –MARCH 2017–REVISED JULY 2018
9.2.3.2.7 Switching FET
Gate-drive voltage for the FET is VDD or about 2 × VDD, if the charge pump is enabled. Use an N-type MOSFET
for the switching FET. The switching FET for SEPIC mode sees a maximum voltage of VIN(max) + VOUT, 25%
higher rating is recommended. Current rating is also recommended to be 25% higher than peak current, which
can be calculated with 公式 19. RDSON must be as low as possible — less than 20 mΩ is recommended. Thermal
resistance (RθJA) must also be low to dissipate heat from power loss on switching FET. Typical rise/fall time
values recommended are less than 10 ns.
IQ1(peak) = IL1(peak) + IL2(peak)
where
•
•
•
IQ1(peak): Peak current for switching FET
IL1(peak): Peak current for inductor 1
IIL2(peak): : Peak current for inductor 2 BOOST_OCP
(19)
9.2.3.2.8 Output Diode
A Schottky diode must be used for the SEPIC output diode. Current rating must be at least 25% higher than the
maximum current, which is the same as switch peak current. Schottky diodes with a low forward drop and fast
switching speeds are ideal for increasing efficiency. At maximum current, the forward voltage must be as low as
possible; TI recommends less than 0.5 V. Reverse breakdown voltage of the Schottky diode must be able to
withstand VIN(max) + VOUT(max); at least 25% higher voltage rating is recommended. Do not use ordinary rectifier
diodes, because slow switching speeds and long recovery times cause efficiency and load regulation to suffer.
9.2.3.2.9 Switching Sense Resistor
See Detailed Design Procedure
9.2.3.2.10 Power-Line FET
See Detailed Design Procedure
9.2.3.2.11 Input Current Sense Resistor
See Detailed Design Procedure
9.2.3.2.12 Feedback Resistor Divider
Feedback resistors RFB1 and RFB2 determine the maximum boost output level. Output voltage can be calculated
as follows:
≈
∆
«
’
VBG
VOUT _MAX
=
+ ISEL_MAX ì RFB1 + VBG
÷
RFB2
◊
where
•
•
•
VBG = 1.21 V
ISEL_MAX = 38.7 µA
RFB2 = 170 kΩ (recommended for SEPIC Mode)
(20)
9.2.3.2.13 Critical Components for Design
图 75 shows the critical part of circuitry: SEPIC components, the LP8863-Q1 internal charge pump for gate-driver
powering, and powering/grounding of LP8863-Q1. Schematic example is shown in 图 70.
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CS2
RS
D1
Q2
L1
RISENSE
VIN
VOUT
COUT
RFB1
RSD
CIN
CS1
L2
CPUMP
CPUMP
CPUMP
Q1
GD
GD
ISNS
C1N
PGND
RSENSE
RFB2
C2x
PGND
ISNSGND
C1P
VDD
FB
VDD
DISCHARGE
GND
CVDD
VLDO
LED0
LED1
LED2
LED3
CLDO
LP8863-Q1
VDDIO
IFSEL
HOST
EN
INT
SDO_PWM
SDI_SDA
LED4
LED5
ISET
SCLK_SCL
SPI
SS_ADDRSEL
RISET
PWM_FSET
BST_FSET
BST_SYNC
RPWM
RBST
Copyright © 2017, Texas Instruments Incorporated
图 75. Critical Components for SEPIC Mode Design
表 55. Recommended Components for SEPIC Design Example
REFERENCE DESIGNATOR
DESCRIPTION
20 mΩ, 3 W
NOTE
RISENSE
RSD
Input current sensing resistor
20 kΩ, 0.1 W
Power-line FET gate pullup resistor
SEPIC current sensing resistor
Bottom feedback divider resistor
Top feedback divider resistor
SEPIC frequency set resistor
Current set resistor for 150 mA max
Output PWM frequency set resistor
Charge pump output capacitor
Flying capacitor
RSENSE
RFB2
RFB1
RBST
RISET
RPWM
CPUMP
C2x
20 mΩ, 3 W
170 kΩ, 0.1 W
560 kΩ, 0.1 W
140 kΩ, 0.1 W
20.5 kΩ, 0.1 W
140 kΩ, 0.1 W
10-µF, 16-V ceramic
2.2-µF, 25-V ceramic
4.7-µF + 0.1-µF, 10-V ceramic
10-µF + 0.1-µF, 10-V ceramic
2 × 33-µF, 63-V electrolytic
2 × 33-µF, 63-V electrolytic
10-µF, 100-V ceramic
33-µF, 63-V electrolytic
2 Ω, 0.125 W
CVDD
CLDO
CIN
VDD bypass capacitor
VLDO bypass capacitor
SEPIC input capacitor
COUT
CS1
SEPIC output capacitor
SEPIC coupling capacitor
SEPIC coupling capacitor
SEPIC resistor
CS2
RS
L1
10-µH saturation current 15.5 A
10-µH saturation current 15.5 A
100-V 10-A Schottky diode
60-V, 25-A nMOSFET
60-V, 30-A pMOSFET
SEPIC inductor
L2
SEPIC inductor
D1
SEPIC Schottky diode
Q1
SEPIC nMOSFET
Q2
Power-line FET
80
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ZHCSGN5B –MARCH 2017–REVISED JULY 2018
9.2.3.3 Application Curves
See Application Curves
10 Power Supply Recommendations
The LP8863-Q1 is designed to operate from a car battery. The VIN input must be protected from reverse voltage
and voltage dump condition over 48 V. The impedance of the input supply rail must be low enough that the input
current transient does not cause drop below VIN UVLO level. If the input supply is connected with long wires,
additional bulk capacitance may be required in addition to normal input capacitor.
The voltage range for VDD is 3 V to 5.5 V. A ceramic capacitor must be placed as close as possible to the VDD
pin. The boost gate driver is powered from the CPUMP pins. A ceramic capacitor must be placed as close to the
CPUMP pins as possible.
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11 Layout
11.1 Layout Guidelines
图 76 shows a layout recommendation for the LP8863-Q1 used to illustrate the principles of good layout. This
layout can be adapted to the actual application layout if and where possible. It is important that all boost
components are close to each other and to the chip; the high-current traces must be wide enough. VDD must be
as noise-free as possible. Place a VDD bypass capacitor near the VDD and GND pins and ground it to a low-
noise ground. A charge-pump capacitor, boost input capacitors, and boost output capacitors must be connected
to PGND. Place the charge-pump capacitors close to the device. The main points to guide the PCB layout
design:
•
Current loops need to be minimized:
–
For low frequency the minimal current loop can be achieved by placing the boost components as close as
possible to each other. Input and output capacitor grounds need to be close to each other to minimize
current loop size.
–
Minimal current loops for high frequencies can be achieved by making sure that the ground plane is intact
under the current traces. High frequency return currents follow the route with minimum impedance, which
is the route with minimum loop area, not necessarily the shortest path. Minimum loop area is formed when
return current flows just under the positive current route in the ground plane, if the ground plane is intact
under the route.
–
For high frequency the copper area capacitance must be taken into account. For example, the copper
area for the drain of boost nMOSFET is a tradeoff between capacitance and the cooling capacity of the
components.
•
•
•
•
GND plane must be intact under the high-current-boost traces to provide shortest possible return path and
smallest possible current loops for high frequencies.
Current loops when the boost switch is conducting and not conducting must be in the same direction in
optimal case.
Inductors must be placed so that the current flows in the same direction as in the current loops. Rotating the
inductor 180° changes current direction.
Use separate power and noise-free grounds. PGND is used for boost converter return current. Use a low-
noise ground for more sensitive signals, like VDD bypass capacitor grounding as well as grounding the GND
pins of the LP8863-Q1 device itself.
•
•
Route boost output voltage (VOUT) to LEDs from output capacitors not straight from the diode cathode.
A small bypass capacitor (TI recommends a 39-pF capacitor) must be placed close to the FB pin to suppress
high frequency noise
•
•
VDD line must be separated from the high current supply path to the boost converter to prevent high
frequency ripple affecting the chip behavior. A separate 1-µF bypass capacitor is used for the VDD pin, and it
is grounded to noise-free ground.
Capacitor connected to charge pump output CPUMP must have 10-µF capacitance, grounded by the shortest
way to boost a switch-current-sensing resistor. This capacitor must be as close as possible to CPUMP pin.
This capacitor provides a greater peak current for gate driver and must be used even if the charge pump is
disabled. If the charge pump is disabled, the VDD and CPUMP pins must be tied together.
•
•
Input and output capacitors need low-impedence grounding (wide traces with many vias to PGND plane).
If two or more output capacitors are used, symmetrical layout must be used to get all capacitors working
ideally.
•
Input/output ceramic capacitors have DC-bias effect. If the output capacitance is too low, it can cause boost
to become unstable under certain load conditions. DC bias characteristics should be obtained from the
component manufacturer; DC bias is not taken into account on component tolerance. TI recommends
X5R/X7R capacitors.
82
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11.2 Layout Example
图 76. LP8863-Q1 Layout Guidelines
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12 器件和文档支持
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All other trademarks are the property of their respective owners.
12.5 静电放电警告
这些装置包含有限的内置 ESD 保护。 存储或装卸时,应将导线一起截短或将装置放置于导电泡棉中,以防止 MOS 门极遭受静电损
伤。
12.6 术语表
SLYZ022 — TI 术语表。
这份术语表列出并解释术语、缩写和定义。
13 机械、封装和可订购信息
以下页面包含机械、封装和可订购信息。这些信息是指定器件的最新可用数据。数据如有变更,恕不另行通知,且
不会对此文档进行修订。如需获取此产品说明书的浏览器版本,请查阅左侧的导航栏。
84
版权 © 2017–2018, Texas Instruments Incorporated
PACKAGE OPTION ADDENDUM
www.ti.com
10-Dec-2020
PACKAGING INFORMATION
Orderable Device
Status Package Type Package Pins Package
Eco Plan
Lead finish/
Ball material
MSL Peak Temp
Op Temp (°C)
Device Marking
Samples
Drawing
Qty
(1)
(2)
(3)
(4/5)
(6)
LP8863ADCPRQ1
ACTIVE
HTSSOP
DCP
38
2000 RoHS & Green
NIPDAU
Level-3-260C-168 HR
-40 to 125
LP8863AQ1
(1) The marketing status values are defined as follows:
ACTIVE: Product device recommended for new designs.
LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect.
NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in a new design.
PREVIEW: Device has been announced but is not in production. Samples may or may not be available.
OBSOLETE: TI has discontinued the production of the device.
(2) RoHS: TI defines "RoHS" to mean semiconductor products that are compliant with the current EU RoHS requirements for all 10 RoHS substances, including the requirement that RoHS substance
do not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered at high temperatures, "RoHS" products are suitable for use in specified lead-free processes. TI may
reference these types of products as "Pb-Free".
RoHS Exempt: TI defines "RoHS Exempt" to mean products that contain lead but are compliant with EU RoHS pursuant to a specific EU RoHS exemption.
Green: TI defines "Green" to mean the content of Chlorine (Cl) and Bromine (Br) based flame retardants meet JS709B low halogen requirements of <=1000ppm threshold. Antimony trioxide based
flame retardants must also meet the <=1000ppm threshold requirement.
(3) MSL, Peak Temp. - The Moisture Sensitivity Level rating according to the JEDEC industry standard classifications, and peak solder temperature.
(4) There may be additional marking, which relates to the logo, the lot trace code information, or the environmental category on the device.
(5) Multiple Device Markings will be inside parentheses. Only one Device Marking contained in parentheses and separated by a "~" will appear on a device. If a line is indented then it is a continuation
of the previous line and the two combined represent the entire Device Marking for that device.
(6)
Lead finish/Ball material - Orderable Devices may have multiple material finish options. Finish options are separated by a vertical ruled line. Lead finish/Ball material values may wrap to two
lines if the finish value exceeds the maximum column width.
Important Information and Disclaimer:The information provided on this page represents TI's knowledge and belief as of the date that it is provided. TI bases its knowledge and belief on information
provided by third parties, and makes no representation or warranty as to the accuracy of such information. Efforts are underway to better integrate information from third parties. TI has taken and
continues to take reasonable steps to provide representative and accurate information but may not have conducted destructive testing or chemical analysis on incoming materials and chemicals.
TI and TI suppliers consider certain information to be proprietary, and thus CAS numbers and other limited information may not be available for release.
In no event shall TI's liability arising out of such information exceed the total purchase price of the TI part(s) at issue in this document sold by TI to Customer on an annual basis.
Addendum-Page 1
PACKAGE MATERIALS INFORMATION
www.ti.com
18-Mar-2019
TAPE AND REEL INFORMATION
*All dimensions are nominal
Device
Package Package Pins
Type Drawing
SPQ
Reel
Reel
A0
B0
K0
P1
W
Pin1
Diameter Width (mm) (mm) (mm) (mm) (mm) Quadrant
(mm) W1 (mm)
LP8863ADCPRQ1
HTSSOP DCP
38
2000
330.0
16.4
6.9
10.2
1.8
12.0
16.0
Q1
Pack Materials-Page 1
PACKAGE MATERIALS INFORMATION
www.ti.com
18-Mar-2019
*All dimensions are nominal
Device
Package Type Package Drawing Pins
HTSSOP DCP 38
SPQ
Length (mm) Width (mm) Height (mm)
350.0 350.0 43.0
LP8863ADCPRQ1
2000
Pack Materials-Page 2
GENERIC PACKAGE VIEW
DCP 38
4.4 x 9.7, 0.5 mm pitch
PowerPAD TSSOP - 1.2 mm max height
SMALL OUTLINE PACKAGE
This image is a representation of the package family, actual package may vary.
Refer to the product data sheet for package details.
4224560/B
www.ti.com
PACKAGE OUTLINE
DCP0038A
PowerPADTM TSSOP - 1.2 mm max height
S
C
A
L
E
2
.
0
0
0
SMALL OUTLINE PACKAGE
C
6.6
6.2
TYP
A
0.1 C
PIN 1 INDEX
AREA
SEATING
PLANE
36X 0.5
38
1
2X
9
9.8
9.6
NOTE 3
19
20
0.27
0.17
0.08
38X
4.5
4.3
B
C A B
SEE DETAIL A
(0.15) TYP
2X 0.95 MAX
NOTE 5
19
20
2X 0.95 MAX
NOTE 5
0.25
GAGE PLANE
1.2 MAX
39
4.70
3.94
THERMAL
PAD
0.15
0.05
0.75
0.50
0 -8
A
20
DETAIL A
TYPICAL
1
38
2.90
2.43
4218816/A 10/2018
PowerPAD is a trademark of Texas Instruments.
NOTES:
1. All linear dimensions are in millimeters. Any dimensions in parenthesis are for reference only. Dimensioning and tolerancing
per ASME Y14.5M.
2. This drawing is subject to change without notice.
3. This dimension does not include mold flash, protrusions, or gate burrs. Mold flash, protrusions, or gate burrs shall not
exceed 0.15 mm per side.
4. Reference JEDEC registration MO-153.
5. Features may differ or may not be present.
www.ti.com
EXAMPLE BOARD LAYOUT
DCP0038A
PowerPADTM TSSOP - 1.2 mm max height
SMALL OUTLINE PACKAGE
(3.4)
NOTE 9
METAL COVERED
BY SOLDER MASK
(2.9)
SYMM
38X (1.5)
38X (0.3)
SEE DETAILS
38
1
(R0.05) TYP
36X (0.5)
3X (1.2)
SYMM
39
(4.7)
(9.7)
NOTE 9
(0.6) TYP
SOLDER MASK
DEFINED PAD
(
0.2) TYP
VIA
20
19
(1.2)
(5.8)
LAND PATTERN EXAMPLE
EXPOSED METAL SHOWN
SCALE: 8X
SOLDER MASK
OPENING
METAL UNDER
SOLDER MASK
SOLDER MASK
OPENING
METAL
EXPOSED METAL
EXPOSED METAL
0.05 MAX
ALL AROUND
0.05 MIN
ALL AROUND
NON-SOLDER MASK
DEFINED
SOLDER MASK
DEFINED
15.000
SOLDER MASK DETAILS
4218816/A 10/2018
NOTES: (continued)
6. Publication IPC-7351 may have alternate designs.
7. Solder mask tolerances between and around signal pads can vary based on board fabrication site.
8. This package is designed to be soldered to a thermal pad on the board. For more information, see Texas Instruments literature
numbers SLMA002 (www.ti.com/lit/slma002) and SLMA004 (www.ti.com/lit/slma004).
9. Size of metal pad may vary due to creepage requirement.
10. Vias are optional depending on application, refer to device data sheet. It is recommended that vias under paste be filled, plugged
or tented.
www.ti.com
EXAMPLE STENCIL DESIGN
DCP0038A
PowerPADTM TSSOP - 1.2 mm max height
SMALL OUTLINE PACKAGE
(2.9)
BASED ON
0.125 THICK
STENCIL
38X (1.5)
38X (0.3)
METAL COVERED
BY SOLDER MASK
1
38
(R0.05) TYP
36X (0.5)
(4.7)
SYMM
39
BASED ON
0.125 THICK
STENCIL
19
20
SYMM
(5.8)
SEE TABLE FOR
DIFFERENT OPENINGS
FOR OTHER STENCIL
THICKNESSES
SOLDER PASTE EXAMPLE
BASED ON 0.125 mm THICK STENCIL
SCALE: 8X
STENCIL
THICKNESS
SOLDER STENCIL
OPENING
0.1
3.24 X 5.25
2.90 X 4.70 (SHOWN)
2.65 X 4.29
0.125
0.15
0.175
2.45 X 3.97
4218816/A 10/2018
NOTES: (continued)
11. Laser cutting apertures with trapezoidal walls and rounded corners may offer better paste release. IPC-7525 may have alternate
design recommendations.
12. Board assembly site may have different recommendations for stencil design.
www.ti.com
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