OPA2604-Q1 [TI]
DUAL FET-INPUT, LOW DISTORTION OPERATIONAL AMPLIFIER;
| 型号： | OPA2604-Q1 |
| 厂家： | 
TEXAS INSTRUMENTS |
| 描述： | DUAL FET-INPUT, LOW DISTORTION OPERATIONAL AMPLIFIER 放大器 输入元件 |
| 文件： | 总16页 (文件大小：310K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
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SGLS209 − NOVEMBER 2003
D PACKAGE
(TOP VIEW)
features
D
Qualification in Accordance With
AEC-Q100
†
OUTPUT A
−IN A
V+
1
2
3
4
8
7
6
5
OUTPUT B
−IN B
D
Qualified for Automotive Applications
+IN A
D
Customer-Specific Configuration Control
Can Be Supported Along With
Major-Change Approval
V−
+IN B
D
D
D
D
D
D
D
Low Distortion: 0.0003% at 1 khz
Low Noise: 10 nV//Hz
(8)
V+
High Slew Rate: 25 V/µs
Wide Gain-Bandwidth: 20 MHz
Unity-Gain Stable
Wide Supply Range: V = 4.5 to 24 V
S
Drives 600 W Loads
(+)
(3, 5)
(−)
†
Distortion
Rejection
Circuitry*
Contact factory for details. Q100 qualification data available on
request.
(1, 7)
VO
Output
Stage*
(2, 6)
applications
D
D
D
D
D
D
Professional Audio Equipment
PCM DAC I/V Converter
Spectral Analysis Equipment
Active Filters
Transducer Amplifier
Data Acquisition
(4)
V−
* Patents Granted:
#5053718, 5019789
description
The OPA2604 is a dual, FET-input operational amplifier designed for enhanced AC performance. Very low
distortion, low noise and wide bandwidth provide superior performance in high quality audio and other
applications requiring excellent dynamic performance.
New circuit techniques and special laser trimming of dynamic circuit performance yield very low harmonic
distortion. The result is an op amp with exceptional sound quality. The low-noise FET input of the OPA2604
provides wide dynamic range, even with high source impedance. Offset voltage is laser-trimmed to minimize
the need for interstage coupling capacitors.
The OPA2604 is available in a SO-8 surface-mount package, specified for the −40°C to +85°C temperature
range.
ORDERING INFORMATION
ORDERABLE
PART NUMBER
TOP-SIDE
MARKING
‡
T
A
PACKAGE
−40°C to 85°C
SOIC - D
Tape and reel
OPA2604IDRQ1
2604Q1
‡
Package drawings, standard packing quantities, thermal data, symbolization, and PCB design
guidelines are available at www.ti.com/sc/package.
Please be aware that an important notice concerning availability, standard warranty, and use in critical applications of
Texas Instruments semiconductor products and disclaimers thereto appears at the end of this data sheet.
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Copyright 2003, Texas Instruments Incorporated
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1
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
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SGLS209 − NOVEMBER 2003
†
absolute maximum ratings over operating free-air temperature (unless otherwise noted)
Power supply voltage . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 25 V
Input voltage, V . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 〈V−) − 1 V to (V+) + 1 V
IN
Output short circuit to ground . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . Continuous
Operating free-air temperature range, T
. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . −40°C to 100°C
A
Storage temperature range, T
. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . −40°C to 125°C
stg
JA
Package thermal impedance, θ (see Note 1): D package . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 90°C/W
Lead temperature 1,6 mm (1/16 inch) from case for 3 seconds . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 260°C
Junction temperature, T . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 150°C
J
†
Stresses beyond those listed under “absolute maximum ratings” may cause permanent damage to the device. These are stress ratings only, and
functional operation of the device at these or any other conditions beyond those indicated under “recommended operating conditions” is not
implied. Exposure to absolute-maximum-rated conditions for extended periods may affect device reliability.
NOTES: 1. The package thermal impedance is calculated in accordance with JESD 51-7.
recommended operating conditions
MIN NOM
MAX
24
UNIT
V
Operating voltage
4.5
15
Operating free-air temperature
−40
85
°C
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SGLS209 − NOVEMBER 2003
electrical characteristics, T = 255C, V = 15 V (unless otherwise noted)
A
S
PARAMETER
Offset Voltage
TEST CONDITIONS
MIN
TYP
MAX
UNIT
Input offset voltage (V
)
1
8
5
mV
µV/°C
dB
IO
Average drift
Power supply rejection ratio (PSRR)
V
S
=
5 V to 24 V
70
80
Input Bias Current (See Note 1)
Input bias current (I
)
V
V
= 0 V
= 0 V
100
4
pA
pA
IB
CM
Input offset current (I
)
IO
CM
Noise
f = 10 Hz
25
15
11
10
1.5
6
f = 100 Hz
Input noise, voltage noise density
nV/√Hz
f = 1 kHz
f = 10 kHz
Voltage noise
BW = 20 Hz to 20 kHz
f = 0.1 Hz to 20 kHz
µV
p-p
Input bias current noise density
Input Voltage Range
fA/√Hz
Common-mode input voltage range
12
80
13
V
(V
ICR
)
Common-mode rejection ratio
(CMRR)
V
CM
=
12 V
100
dB
Input Impedance
12
10
Ω
pF
Input impedance, differential mode
8
12
10
10
Ω
pF
Input impedance, common mode
Open-loop Gain
Open-loop voltage gain (AVOL)
Frequency Response
Gain bandwidth product
Slew rate
V
=
10 V,
R
= 1 kΩ
L
80
15
100
dB
O
G = 100
20
25
1.5
1
MHz
V/µs
µs
20 V , R = 1 kΩ
p-p
L
Settling time to 0.01%
Settling time to 0.1%
G = −1, 10 V step
µs
Total Harmonic Distortion + Noise
(THD+N)
G = 1,
f = 1 kHz,
V
= 3.5 Vrms,
R
L
= 1 kΩ
0.0003
142
%
O
Channel separation
f = 1 kHz,
R
= 1 kΩ
dB
L
Output
Output voltage range (V
, V
)
R
= 600 Ω
11
12
35
40
25
V
OH OL
L
Output current (I
)
V
O
=
12 V
mA
mA
Ω
O
Output short circuit current (I
)
OS
Open-loop output resistance
Power Supply
Total current. both amplifiers (I
CC
)
I
O
= 0
10.5
12
mA
NOTE 1: Typical performance, measured fully warmed-up.
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SGLS209 − NOVEMBER 2003
TYPICAL CHARACTERISTICS
TOTAL HARMONIC DISTORTION + NOISE
vs OUTPUT VOLTAGE
TOTAL HARMONIC DISTORTION + NOISE
vs FREQUENCY
0.1
0.01
1
0.1
See ”Distortion Measurements”
for description of test method.
Measurement BW = 80kHz
See ”Distortion Measure−
ments” for desription of
test method.
VO
VO =
3.5Vrms
Ω
Ω
1k
1k
f = 1kHz
G = 100V/V
G = 10V/V
Measurement BW = 80kHz
0.01
0.001
0.001
0.0001
G = 1V/V
0.0001
0.1
1
10
100
20
100
1k
10k 20k
Output Voltage (Vp−p)
Frequency (Hz)
Figure 1
Figure 2
INPUT VOLTAGE AND CURRENT NOISE
SPECTRAL DENSITY vs FREQUENCY
OPEN−LOOP GAIN/PHASE vs FREQUENCY
0
120
1k
100
10
1k
100
10
1
100
80
60
40
20
0
−45
−90
−135
−180
φ
Voltage Noise
G
Current Noise
−20
1
1
10
100
1k
10k
100k
1M
10M
1
10
100
1k
10k
100k
1M
Frequency (Hz)
Frequency (Hz)
Figure 4
Figure 3
INPUT BIAS AND INPUT OFFSET CURRENT
vs INPUT COMMON−MODE VOLTAGE
INPUT BIAS AND INPUT OFFSET CURRENT
vs TEMPERATURE
10nA
1nA
100
10
1nA
100
10
100nA
10nA
1nA
100
10nA
1nA
100
10
Input
Bias Current
Input
Bias Current
Input
Offset Current
10
1
Input
Offset Current
1
15
1
0.1
−15
−10
−5
0
5
10
−75
−50
−25
0
25
50
75
100
125
Common−Mode Voltage (V)
Ambient Temperature (°C)
Figure 5
Figure 6
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SGLS209 − NOVEMBER 2003
TYPICAL CHARACTERISTICS
COMMON−MODE REJECTION
vs COMMON−MODE VOLTAGE
INPUT BIAS CURRENT
vs TIME FROM POWER TURN−ON
120
110
100
90
1nA
100
10
VS = 24VDC
VS = 15VDC
VS = 5VDC
80
1
−15
−10
−5
0
5
10
15
0
1
2
3
4
5
Common−Mode Voltage (V)
Time After Power Turn−On (min)
Figure 7
Figure 8
POWER SUPPLY AND COMMON−MODE
REJECTION vs FREQUENCY
AOL, PSR, AND CMR vs SUPPLY VOLTAGE
120
110
100
90
120
100
80
60
40
20
0
CMR
CMR
AOL
−PSR
+PSR
80
PSR
70
5
10
15
20
25
10
100
1k
10k
100k
1M
10M
Supply Voltage ( VS)
Frequency (Hz)
Figure 9
Figure 10
GAIN−BANDWIDTH AND SLEW RATE
vs TEMPERATURE
GAIN−BANDWIDTH AND SLEW RATE
vs SUPPLY VOLTAGE
28
24
20
16
12
30
28
24
20
16
12
33
Slew Rate
25
20
15
10
29
25
21
17
Gain−Bandwidth
G = +100
Slew Rate
Gain−Bandwidth
G = +100
−75
−50
−25
0
25
50
75
100
125
5
10
15
20
25
Temperature (°C)
Supply Voltage ( VS)
Figure 11
Figure 12
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SGLS209 − NOVEMBER 2003
TYPICAL CHARACTERISTICS
CHANNEL SEPARATION vs FREQUENCY
SETTLING TIME vs CLOSED−LOOP GAIN
160
140
120
100
80
5
4
3
2
1
0
VO = 10V Step
RL = 1kΩ
CL = 50pF
RL = ∞
RL = 1kΩ
0.01%
0.1%
VO =
20Vp−p
A
B
RL
Measured
Output
10
100
1k
10k
100k
−1
−10
−100
−1000
Frequency (Hz)
Closed−Loop Gain (V/V)
Figure 13
Figure 14
MAXIMUM OUTPUT VOLTAGE SWING vs FREQUENCY
SUPPLY CURRENT vs TEMPERATURE
Total for Both Op Amps
30
20
10
0
14
12
10
8
V
=
15 V
S
VS = 15VDC
VS = 24VDC
VS = 5VDC
6
10k
100k
Frequency (Hz)
1M
10M
−75
−50
−25
0
25
50
75
100
125
Ambient Temperaturre (°C)
Figure 15
Figure 16
SMALL−SIGNAL TRANSIENT RESPONSE
LARGE−SIGNAL TRANSIENT RESPONSE
+100
+10
−100
−10
0
µ
µ
s
1
s
2
0
5
10
Time ( us)
Time ( us)
Figure 17
Figure 18
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POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
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SGLS209 − NOVEMBER 2003
TYPICAL CHARACTERISTICS
POWER DISSIPATION vs SUPPLY VOLTAGE
SHORT−CIRCUIT CURRENT vs TEMPERATURE
ISC+ and ISC−
1
0.9
0.8
0.7
0.6
0.5
0.4
0.3
0.2
0.1
60
50
40
30
20
Worst case sine
wave RL = 600Ω
(both channels)
Typical high−level
music RL = 600Ω
(both channels)
No signal
or no load
6
8
10
12
14
16
18
20
22
24
−75
−50
−25
0
25
50
75
100
125
Supply Voltage, VS (V)
Ambient Temperature (°C)
Figure 19
Figure 20
MAXIMUM POWER DISSIPATION vs TEMPERATURE
1.4
1.2
1.0
0.8
0.6
0.4
0.2
0
θJ−A = 90°C/W
Soldered to
Circuit Board
(see text)
Maximum
Specified Operating
Temperature
85°C
0
25
50
75
100
125
150
Ambient Temperature (°C)
Figure 21
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SGLS209 − NOVEMBER 2003
APPLICATION INFORMATION
The OPA2604 is unity-gain stable, making it easy to use in a wide range of circuitry. Applications with noisy or
high impedance power supply lines may require decoupling capacitors close to the device pins. In most cases
1 µF tantalum capacitors are adequate.
distortion measurements
The distortion produced by the OPA2604 is below the measurement limit of virtually all commercially available
equipment. A special test circuit, however, can be used to extend the measurement capabilities.
Op amp distortion can be considered an internal error source which can be referred to the input. Figure 22
shows a circuit which causes the op amp distortion to be 101 times greater than normally produced by the op
amp. The addition of R to the otherwise standard non-inverting amplifier configuration alters the feedback
3
factor or noise gain of the circuit. The closed-loop gain is unchanged, but the feedback available for error
correction is reduced by a factor of 101. This extends the measurement limit, including the effects of the
signal-source purity, by a factor of 101. Note that the input signal and load applied to the op amp are the same
as with conventional feedback without R .
3
Validity of this technique can be verified by duplicating measurements at high gain and/or high frequency where
the distortion is within the measurement capability of the test equipment. Measurements for this data sheet were
made with the Audio Precision System One which greatly simplifies such repetitive measurements. The
measurement technique can, however, be performed with manual distortion measurement instruments.
R1
R2
SIG. DIST.
GAIN GAIN
R1
R2
R3
∞
5kΩ
50Ω
1
101
101
101
1 2
R3
VO = 10Vp−p
(3.5Vrms)
OPA2604
500Ω 5kΩ 500Ω
10
50Ω
5kΩ
∞
100
Generator
Output
Analyzer
Input
RL
1kΩ
Audio Precision
System One
Analyzer*
IBM PC
or
Compatible
* Measurement BW = 80kHz
Figure 22. Distortion Test Circuit
capacitive loads
The dynamic characteristics of the OPA2604 have been optimized for commonly encountered gains, loads and
operating conditions. The combination of low closed-loop gain and capacitive load will decrease the phase
margin and may lead to gain peaking or oscillations. Load capacitance reacts with the op amp’s open-loop
output resistance to form an additional pole in the feedback loop. Figure 23 shows various circuits which
preserve phase margin with capacitive load. Request Application Bulletin AB-028 for details of analysis
techniques and applications circuits.
For the unity-gain buffer, Figure a, stability is preserved by adding a phase-lead network, R and C . Voltage
C
C
drop across R will reduce output voltage swing with heavy loads. An alternate circuit, Figure b, does not limit
C
the output with low load impedance. It provides a small amount of positive feed-back to reduce the net feedback
factor. Input impedance of this circuit falls at high frequency as op amp gain rolloff reduces the bootstrap action
on the compensation network.
8
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
ꢀ
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ꢄ
ꢅ
ꢆ
ꢊꢋꢂ ꢌ ꢍ ꢎꢏꢇꢐ ꢑꢁꢋꢏꢒ ꢌ ꢀꢓ ꢊꢐ ꢔꢏꢀ ꢕꢏ ꢐ ꢀ
ꢇ
ꢈ
ꢉ
ꢑ
ꢕ
ꢀ
ꢁ
ꢎ
ꢕ
ꢂꢏ
ꢐ
ꢀ
ꢑ
ꢂ
ꢌ
ꢂ
ꢖ
ꢁ
ꢌ
ꢐ
ꢍ
ꢐ
ꢎ
SGLS209 − NOVEMBER 2003
Figures c and d show compensation techniques for noninverting amplifiers. Like the follower circuits, the circuit
in Figure d eliminates voltage drop due to load current, but at the penalty of somewhat reduced input impedance
at high frequency.
Figures e and f show input lead compensation networks for inverting and difference amplifier configurations.
9
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
ꢀꢁꢂ ꢃꢄ ꢅ ꢆꢇꢈꢉ
ꢌ
ꢊ
ꢋ
ꢂ
ꢍ
ꢎ
ꢏ
ꢇ
ꢐ
ꢑ
ꢁ
ꢋ
ꢏꢒ
ꢌꢀ
ꢓ
ꢊ
ꢐ
ꢔ
ꢏꢀ
ꢕ
ꢏ
ꢐ
ꢀ
ꢑ
ꢀ
ꢁ
ꢎ
ꢕ
ꢂ
ꢏ
ꢐ
ꢀ
ꢑ
ꢂ
ꢌ
ꢂ
ꢖ
ꢁꢌ
ꢐ
ꢍ
ꢐ
ꢎ
ꢕ
SGLS209 − NOVEMBER 2003
(a)
(b)
CC
820pF
RC
1 2
eo
OPA2604
1 2
eo
OPA2604
ei
750Ω
CL
CC
5000pF
0.47uF
CL
5000pF
R2
RC
ei
CC = 120 X 10−12 CL
2kΩ
10Ω
R2
RC =
CC =
4CL X 1010 − 1
CL X 103
RC
(c)
(d)
R1
R2
R1
2kΩ
R2
2kΩ
10kΩ
10kΩ
CC
RC
20Ω
24pF
CC
0.22uF
RC
1 2
1 2
eo
eo
OPA2604
OPA2604
ei
25Ω
ei
CL
5000pF
CL
5000pF
R2
50
RC =
CC =
CL
2CL X 1010 − (1 + R2/R1)
R2
CL X 103
RC
CC =
(e)
(f)
R2
R1
R2
e1
2kΩ
2kΩ
2kΩ
R1
RC
ei
20Ω
1 2
1 2
2kΩ
eo
eo
OPA2604
OPA2604
CC
RC
20Ω
0.22uF
CL
5000pF
CL
5000pF
R3
R4
CC
0.22uF
e2
2kΩ
2kΩ
R2
RC =
CC =
2CL X 1010 − (1 + R2/R1)
R2
RC =
2CL X 1010 − (1 + R2/R1)
CL X 103
RC
CL X 103
RC
CC =
Figure 23. Driving Large Capacitive Loads
10
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
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ꢇ
ꢈ
ꢉ
ꢑ
ꢕ
ꢀ
ꢁ
ꢎ
ꢕ
ꢂꢏ
ꢐ
ꢀ
ꢑ
ꢂ
ꢌ
ꢂ
ꢖ
ꢁ
ꢌ
ꢐ
ꢍ
ꢐ
ꢎ
SGLS209 − NOVEMBER 2003
noise performance
Op amp noise is described by two parameters − noise voltage and noise current. The voltage noise determines
the noise performance with low source impedance. Low noise bipolar-input op amps such as the OPA27 and
OPA37 provide very low voltage noise. But if source impedance is greater than a few thousand ohms, the current
noise of bipolar-input op amps react with the source impedance and will dominate. At a few thousand ohms
source impedance and above, the OPA2604 will generally provide lower noise.
power dissipation
The OPA2604 is capable of driving 600 Ω loads with power supply voltages up to 24 V. Internal power
dissipation is increased when operating at high power supply voltage. The typical performance curve, Power
Dissipation vs Power Supply Voltage, shows quiescent dissipation (no signal or no load) as well as dissipation
with a worst case continuous sine wave. Continuous high-level music signals typically produce dissipation
significantly less than worst case sine waves.
Copper leadframe construction used in the OPA2604 improves heat dissipation compared to conventional
plastic packages. To achieve best heat dissipation, solder the device directly to the circuit board and use wide
circuit board traces.
output current limit
Output current is limited by internal circuitry to approximately 40 mA at 25°C. The limit current decreases with
increasing temperature as shown in the typical curves.
R4
22kΩ
C3
100pF
R1
R2
R3
VIN
1 2
VO
2.7kΩ
22kΩ
10kΩ
OPA2604
C1
C2
3000pF
2000pF
fp = 20kHz
Figure 24. Three-Pole Low-Pass Filter
11
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
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ꢊ
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ꢍ
ꢎ
ꢏ
ꢇ
ꢐ
ꢑ
ꢁ
ꢋ
ꢏ
ꢒ
ꢌ
ꢀ
ꢓ
ꢊ
ꢀꢁ ꢎ ꢕꢂꢏ ꢐ ꢀꢑ ꢂ ꢌ ꢂꢖ ꢁꢌ ꢐ ꢍꢐ ꢎ
ꢐ
ꢕ
ꢔ
ꢏꢀ
ꢕ
ꢏ
ꢐ
ꢀ
ꢑ
SGLS209 − NOVEMBER 2003
1 2
R1
R5
VO
OPA2604
VIN
6.04kΩ
2kΩ
R2
C3
4.02kΩ
1000pF
R2
Low−pass
3−pole Butterworth
f−3dB = 40kHz
4.02kΩ
1 2
OPA2604
1 2
OPA2604
C1
1000pF
R4
5.36kΩ
See Application Bulletin AB−026
for information on GIC filters.
C2
1000pF
Figure 25. Three-Pole Generalized Immittance Converter (GIC) Low-Pass Filter
C1*
I−Out DAC
R1
C2
2200pF
2kΩ
1 2
R2
R3
VO
OPA2604
1 2
OPA2604
COUT
2.94kΩ
21kΩ
C3
470pF
Low−pass
2−pole Butterworth
f−3dB = 20kHz
COUT
2π R1 fc
~
* C1 =
R1 = Feedback resistance = 2kΩ
fc = Crossover frequency = 8MHz
Figure 26. DAC I/V Amplifier and Low-Pass Filter
12
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
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ꢊꢋꢂ ꢌ ꢍ ꢎꢏꢇꢐ ꢑꢁꢋꢏꢒ ꢌ ꢀꢓ ꢊꢐ ꢔꢏꢀ ꢕꢏ ꢐ ꢀ
ꢇ
ꢈ
ꢉ
ꢑ
ꢕ
ꢀ
ꢁ
ꢎ
ꢕ
ꢂꢏ
ꢐ
ꢀ
ꢑ
ꢂ
ꢌ
ꢂ
ꢖ
ꢁ
ꢌ
ꢐ
ꢍ
ꢐ
ꢎ
SGLS209 − NOVEMBER 2003
10kΩ
10kΩ
1 2
7.87kΩ
OPA2604
−
VIN
+
1 2
100pF
VO
G = 1
OPA2604
1 2
7.87kΩ
100kHz Input Filter
OPA2604
10kΩ
10kΩ
Figure 27. Differential Amplifier with Low-Pass Filter
COUT
2π Rf fc
100Ω
10kΩ
* C1 ≈
Rf = Internal feedback resistance = 1.5kΩ
fc = Crossover frequency = 8MHz
G = 101
(40dB)
1 2
10
5
OPA2604
C1*
PCM63
20−bit
Piezoelectric
Transducer
6
1 2
D/A
Converter
1MΩ*
9
VO = 3Vp
OPA2604
To low−pass
filter.
* Provides input bias
current return path.
Figure 28. High Impedance Amplifier
Figure 29. Digital Audio DAC I-V Amplifier
1/2 OPA2604
A2
I2
R4
1/2 OPA2604
A1
51Ω
R3
51Ω
IL = I1 + I2
i1
VIN
R2
VOUT
Load
R1
VOUT = VIN (1 + R2/R1)
Figure 30. Using the Dual OPA2604 Op Amp to Double the Output Current to a Load
13
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
PACKAGE OPTION ADDENDUM
www.ti.com
18-Sep-2008
PACKAGING INFORMATION
Orderable Device
Status (1)
Package Package
Pins Package Eco Plan (2) Lead/Ball Finish MSL Peak Temp (3)
Qty
Type
Drawing
OPA2604IDRQ1
OBSOLETE
SOIC
D
8
TBD
Call TI
Call TI
(1) The marketing status values are defined as follows:
ACTIVE: Product device recommended for new designs.
LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect.
NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in
a new design.
PREVIEW: Device has been announced but is not in production. Samples may or may not be available.
OBSOLETE: TI has discontinued the production of the device.
(2)
Eco Plan - The planned eco-friendly classification: Pb-Free (RoHS), Pb-Free (RoHS Exempt), or Green (RoHS & no Sb/Br) - please check
http://www.ti.com/productcontent for the latest availability information and additional product content details.
TBD: The Pb-Free/Green conversion plan has not been defined.
Pb-Free (RoHS): TI's terms "Lead-Free" or "Pb-Free" mean semiconductor products that are compatible with the current RoHS requirements
for all 6 substances, including the requirement that lead not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered
at high temperatures, TI Pb-Free products are suitable for use in specified lead-free processes.
Pb-Free (RoHS Exempt): This component has a RoHS exemption for either 1) lead-based flip-chip solder bumps used between the die and
package, or 2) lead-based die adhesive used between the die and leadframe. The component is otherwise considered Pb-Free (RoHS
compatible) as defined above.
Green (RoHS & no Sb/Br): TI defines "Green" to mean Pb-Free (RoHS compatible), and free of Bromine (Br) and Antimony (Sb) based flame
retardants (Br or Sb do not exceed 0.1% by weight in homogeneous material)
(3)
MSL, Peak Temp. -- The Moisture Sensitivity Level rating according to the JEDEC industry standard classifications, and peak solder
temperature.
Important Information and Disclaimer:The information provided on this page represents TI's knowledge and belief as of the date that it is
provided. TI bases its knowledge and belief on information provided by third parties, and makes no representation or warranty as to the
accuracy of such information. Efforts are underway to better integrate information from third parties. TI has taken and continues to take
reasonable steps to provide representative and accurate information but may not have conducted destructive testing or chemical analysis on
incoming materials and chemicals. TI and TI suppliers consider certain information to be proprietary, and thus CAS numbers and other limited
information may not be available for release.
In no event shall TI's liability arising out of such information exceed the total purchase price of the TI part(s) at issue in this document sold by TI
to Customer on an annual basis.
OTHER QUALIFIED VERSIONS OF OPA2604-Q1 :
Catalog: OPA2604
•
NOTE: Qualified Version Definitions:
Catalog - TI's standard catalog product
•
Addendum-Page 1
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