PTH08T240WAS_技术文档

PTH08T240W

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SLTS264A–NOVEMBER 2005–REVISED MARCH 2006

10-A, 4.5-V to 14-V INPUT, NON-ISOLATED,

WIDE-OUTPUT, ADJUSTABLE POWER MODULE WITH TURBOTRANS™

FEATURES

•

Up to 10-A Output Current

4.5-V to 14-V Input Voltage

•

TurboTrans™ Technology

Designed to meet Ultra-Fast Transient

Requirements up to 300 A/µs

Wide-Output Voltage Adjust (0.69 V to 5.5 V)

±1.5% Total Output Voltage Variation

Efficiencies up to 96%

Output Overcurrent Protection

(Nonlatching, Auto-Reset)

APPLICATIONS

•

Complex Multi-Voltage Systems

Microprocessors

Bus Drivers

•

Operating Temperature: –40°C to 85°C

Safety Agency Approvals:

– UL 1950, CSA 22.2 950, EN60950 VDE

(Pending)

•

On/Off Inhibit

Differential Output Voltage Remote Sense

Adjustable Undervoltage Lockout

SmartSync Technology

Auto-Track™ Sequencing

DESCRIPTION

The PTH08T240W is a high-performance 10-A rated, non-isolated power module. This module represents the

2nd generation of the PTH series power modules which includes a reduced footprint and additional features.

Operating from an input voltage range of 4.5 V to 14 V, the PTH08T240W requires a single resistor to set the

output voltage to any value over the range, 0.69 V to 5.5 V. The wide input voltage range makes the

PTH08T240W particularly suitable for advanced computing and server applications that utilize a loosely

regulated 8-V to 12-V intermediate distribution bus. Additionally, the wide input voltage range increases design

flexibility by supporting operation with tightly regulated 5-V, 8-V, or 12-V intermediate bus architectures.

The module incorporates a comprehensive list of features. Output over-current and over-temperature shutdown

protects against most load faults. A differential remote sense ensures tight load regulation. An adjustable

under-voltage lockout allows the turn-on voltage threshold to be customized. Auto-Track™sequencing is a

popular feature that greatly simplifies the simultaneous power-up and power-down of multiple modules in a

power system.

The PTH08T240W includes new patent pending technologies, TurboTrans™ and SmartSync. The TurboTrans

feature optimizes the transient response of the regulator while simultaneously reducing the quantity of external

output capacitors required to meet a target voltage deviation specification. Additionally, for a target output

capacitor bank, TurboTrans can be used to significantly improve the regulators transient response by reducing

the peak voltage deviation. SmartSync allows for switching frequency synchronization of multiple modules, thus

simplifying EMI noise suppression tasks and/or reducing input capacitor RMS current requirements.

The module uses double-sided surface mount construction to provide a low profile and compact footprint.

Package options include both through-hole and surface mount configurations that are lead (Pb) - free and RoHS

compatible.

Please be aware that an important notice concerning availability, standard warranty, and use in critical applications of Texas

Instruments semiconductor products and disclaimers thereto appears at the end of this data sheet.

Auto-Track, TurboTrans, TMS320 are trademarks of Texas Instruments.

PRODUCTION DATA information is current as of publication date.

Products conform to specifications per the terms of the Texas

Instruments standard warranty. Production processing does not

necessarily include testing of all parameters.

PTH08T240W

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SLTS264A–NOVEMBER 2005–REVISED MARCH 2006

These devices have limited built-in ESD protection. The leads should be shorted together or the device placed in conductive foam

during storage or handling to prevent electrostatic damage to the MOS gates.

SmartSync

Track

TurboTranst

R

TT

1%

10

1

9

0.05 W

(Optional)

Track SYNC

TT

+Sense

VI

6

5

7

+Sense

2

V

I

V

O

V

O

PTH08T240W

Inhibit

11

INH/UVLO

GND

−Sense

L

O

A

D

GND

4

V Adj

O

+

C

O

3

8

R

220 µF

(Required)

SET

C 2

22 µF

(Optional)

R

C

I

1%

I

UVLO

1%

220 µF

0.05 W

(Required)

−Sense

(Opional)

GND

UDG−06005

A. R_SETrequired to set the output voltage to a value higher than 0.69 V. See Electrical Characteristics table.

B. When V_O> 3.3 V the minimum required output capacitance increases to 330 µF.

ORDERING INFORMATION

For the most current package and ordering information, see the Package Option Addendum at the end of this datasheet, or see the TI

website at www.ti.com.

ENVIRONMENTAL AND ABSOLUTE MAXIMUM RATINGS

(Voltages are with respect to GND)

UNIT

V_I

Input voltage

Track

–0.3 to V_I+ 0.3

–40 to 85

235

V

T_A

Operating temperature range Over V_Irange

PTH08T240WAH

PTH08T240WAD

PTH08T240WAS

PTH08T240WAZ

Surace temperature of module body or pins for

5 seconds maximum.

T_waveWave soldering temperature

T_reflowSolder reflow temperature

260

°C

235⁽¹⁾

260⁽¹⁾

–40 to 125

TBD

Surface temperature of module body or pins

T_stg

Storage temperature

Mechanical shock

Per Mil-STD-883D, Method 2002.3 1 mssec, 1/2 sine, mounted

Suffix AH and AD

Suffix AS and AZ

TBD

G

Mechanical vibration

Mil-STD-883D, Method 2007.2 20-2000 Hz

TBD

Weight

5

grams

Flammability

Meets UL94V-O

(1) During reflow of surface mount package version do not elevate peak temperature of the module, pins or internal components above the

stated maximum.

2

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ELECTRICAL CHARACTERISTICS

T_A= 25°C, V_I= 5 V, V_O= 3.3 V, C_I= 220 µF, C_O= 220 µF, and I_O= I_Omax (unless otherwise stated)

PARAMETER

Output current

TEST CONDITIONS

MIN

TYP

MAX

10

UNIT

I_O

0.7 V ≤ V_O≤ 3.6 V 25°C, natural convection

0

A

11 ×

0.69 ≤ V_O≤ 1.2

4.5

(1)

V_O

V_I

Input voltage range

Over I_Orange

V

1.2 < V_O≤ 3.6

3.6 < V_O≤ 5.5

4.5

V_O+ 2

0.69

14

V_OADJ

Output voltage adjust range

Set-point voltage tolerance

Temperature variation

Line regulaltion

5.5

V

(2)

±0.5

±0.3

±3

±1

%V_o

mV

–40°C < T_A< 85°C

Over V_Irange

V_O

Load regulation

Over I_Orange

±2

mV

(2)

Total output variation

Includes set-point, line, load, –40°C ≤ T_A≤ 85°C

R_SET= 1.21 kΩ, V_O= 3.3 V

±1.5

%V_o

94%

92%

90%

88%

87%

85%

10

R_SET= 2.38 kΩ, V_O= 2.5 V

R_SET= 4.78 kΩ, V_O= 1.8 V

η

Efficiency

I_O= 10 A

R_SET= 7.09 kΩ, V_O= 1.5 V

R_SET= 12.1 kΩ, V_O= 1.2 V

R_SET= 20.8 kΩ, V_O= 1.0 V

V_ORipple (peak-to-peak)

Overcurrent threshold

20-MHz bandwidth

mV_PP

A

I_LIM

t_tr

Reset, followed by auto-recovery

20

Recovery time

V_Oover/undershoot

Recovery time

35

µs

w/o Turbotrans

CO = 220 µF, Type C

∆V_tr

t_trTT

2.5 A/µs load step

50 to 100% I_Omax

V_O= 2.5 V

165

130

mV

µs

Transient response

w/ TurboTrans

C_O= 2000 µF, Type C,

mV

∆V_trTT

V_Oover/undershoot

30

R_TT= 0 Ω

I_IL

Track input current (pin 10)

Pin to GND

–130⁽³⁾

1

µA

dV_track/dt Track slew rate capability

C_O≤ C_O(max)

V/ms

V_Iincreasing, R_UVLO= OPEN

V_idecreasing, R_UVLO= OPEN

Hysterisis, R_UVLO≤ 52.3 kΩ

4.3

4.2

0.5

4.45

Adjustable Under-voltage lockout

UVLO_ADJ

(pin 11)

4.0

V

Input high voltage (V_IH

)

V_I– 0.5

-0.2

Open⁽⁴⁾

0.8

V

Inhibit control (pin 11)

Input low voltage (V_IL)

Input low current (I_IL), Pin 11 to GND

Inhibit (pin 11) to GND, Track (pin 10) open

Over V_Iand I_Oranges

-235

5

µA

mA

kHz

I_in

Input standby current

Switching frequency

f _s

300

Synchronization (SYNC)

frequency

f_SYNC

240

2

400

kHz

V_SYNCH

V_SYNCL

t_SYNC

SYNC High-Level Input Voltage

SYNC Low-Level Input Voltage

SYNC Minimum Pulse Width

5.5

0.8

V

200

nSec

(5)

Nonceramic

Ceramic

220

C_I

External input capacitance

µF

(5)

22

(1) The maximum input voltage is duty cycle limited to (V_O× 11) or 14 volts, whichever is less. The maximum allowable input voltage is a

function of switching frequency, and may increase or decrease when the SmartSync feature is utilized. Please review the SmartSync

section of the Application Information for further guidance.

(2) The set-point voltage tolerance is affected by the tolerance and stability of R_SET. The stated limit is unconditionally met if R_SEThas a

tolerance of 1% with 100 ppm/°C or better temperature stability.

(3) A low-leakage (<100 nA), open-drain device, such as MOSFET or voltage supervisor IC, is recommended to control pin 10. The

open-circuit voltage is less than 8 V_dc

.

(4) This control pin has an internal pull-up. Do not place an external pull-up on this pin. If it is left open-circuit, the module operates when

input power is applied. A small, low-leakage (<100 nA) MOSFET is recommended for control. For additional information, see the related

application note.

(5) A 220 µF electrolytic input capacitor is required for proper operation. The electrolytic capacitor must be rated for a minimum of 500 mA

rms of ripple current.

3

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ELECTRICAL CHARACTERISTICS (continued)

T_A= 25°C, V_I= 5 V, V_O= 3.3 V, C_I= 220 µF, C_O= 220 µF, and I_O= I_Omax (unless otherwise stated)

PARAMETER

TEST CONDITIONS

MIN

TYP

MAX

UNIT

(6)

(7)

Nonceramic

Ceramic

220

5000

Capacitance Value

µF

w/o TurboTrans

w/ TurboTrans

TBD

Equivalent series resistance (non-ceramic)

TBD

mΩ

µF

C_O

External output capacitance

see table

Capacitance Value

(6)(8)

(8)

Capacitance × ESR product (C_O× ESR)

10000

µF×mΩ

10⁶Hr

Per Bellcore TR-332, 50% stress,

T_A= 40°C, ground benign

MTBF

Reliability

TBD

(6) For V_O≤ 3.3 V, a 220 µF external output capacitor is required for basic operation. When V_O> 3.3 V the minimum output capacitance

increase to 330 µF. The minimum output capacitance requirement increases when TurboTrans™ (TT) technology is utilized. See related

Application Information for more guidance.

(7) This is the calculated maximum disregarding TurboTrans™ technology. When the TurboTrans™ feature is utilized, the minimum output

capacitance must be increased.

(8) When using TurboTrans™ technology, a minimum value of output capacitance is required for proper operation. Additionally, low ESR

capacitors are required for proper operation. See the application notes for further guidance.

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TERMINAL

SLTS264A–NOVEMBER 2005–REVISED MARCH 2006

TERMINAL FUNCTIONS

DESCRIPTION

NAME

NO.

2

V_I

The positive input voltage power node to the module, which is referenced to common GND.

The regulated positive power output with respect to the GND.

V_O

5

This is the common ground connection for the V_Iand V_Opower connections. It is also the 0 V_dcreference for the

control inputs.

GND

3, 4

The Inhibit pin is an open-collector/drain, negative logic input that is referenced to GND. Applying a low level

ground signal to this input disables the module’s output and turns off the output voltage. When the Inhibit control

is active, the input current drawn by the regulator is significantly reduced. If the Inhibit pin is left open-circuit, the

module produces an output whenever a valid input source is applied.

Inhibit⁽¹⁾and

UVLO

11

This pin is also used for input undervoltage lockout (UVLO) programming. Connecting a resistor from this pin to

GND (pin 3) allows the ON threshold of the UVLO to be adjusted higher than the default value. For more

information, see the Application Information section.

A 0.05 W 1% resistor must be directly connected between this pin and pin 7 (–Sense) to set the output voltage

to a value higher than 0.69 V. The temperature stability of the resistor should be 100 ppm/°C (or better). The

setpoint range for the output voltage is from 0.69 V to 5.5 V. If left open circuit, the output voltage will default to

its lowest value. For further information, on output voltage adjustment see the related application note.

V_oAdjust

8

The specification table gives the preferred resistor values for a number of standard output voltages.

The sense input allows the regulation circuit to compensate for voltage drop between the module and the load.

For optimal voltage accuracy, +Sense must be connected to V_O, very close to the load.

+ Sense

– Sense

6

7

The sense input allows the regulation circuit to compensate for voltage drop between the module and the load.

For optimal voltage accuracy, –Sense must be connected to GND (pin 4), very close to the load.

This is an analog control input that enables the output voltage to follow an external voltage. This pin becomes

active typically 20 ms after the input voltage has been applied, and allows direct control of the output voltage

from 0 V up to the nominal set-point voltage. Within this range the module's output voltage follows the voltage at

the Track pin on a volt-for-volt basis. When the control voltage is raised above this range, the module regulates

at its set-point voltage. The feature allows the output voltage to rise simultaneously with other modules powered

from the same input bus. If unused, this input should be connected to V_I.

Track

10

NOTE: Due to the undervoltage lockout feature, the output of the module cannot follow its own input voltage

during power up. For more information, see the related application note.

This input pin adjusts the transient response of the regulator. To activate the TurboTrans™ feature, a 1%,

50 mW resistor must be connected between this pin and pin 6 (+Sense) very close to the module. For a given

value of output capacitance, a reduction in peak output voltage deviation is achieved by utililizing this feature. If

unused, this pin must be left open-circuit. The resistance requirement can be selected from the TurboTrans™

resistor table in the Application Information section. External capacitance must never be connected to this pin

unless the TurboTrans resistor value is a short, 0Ω.

TurboTrans™

9

1

This input pin sychronizes the switching frequency of the module to an external clock frequency. The SmartSync

feature can be used to sychronize the switching fequency of multiple PTH08T240W modules, aiding EMI noise

suppression efforts. If unused, this pin should be connected to GND (pin 3). For more information, please review

the Application Information section.

SmartSync

(1) Denotes negative logic: Open = Normal operation, Ground = Function active

11

1

10

9

2

8

7

PTH08T240W

(Top View)

6

3

4

5

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(1)(2)

TYPICAL CHARACTERISTICS

CHARACTERISTIC DATA ( V_I= 12 V)

EFFICIENCY

vs

LOAD CURRENT

OUTPUT RIPPLE

vs

LOAD CURRENT

POWER DISSIPATION

vs

LOAD CURRENT

16

4.0

3.5

3.0

2.5

2.0

1.5

1.0

0.5

0

100

90

80

70

60

50

40

30

20

V

= 2.5 V

O

V

O

= 5.0 V

14

12

V

= 5.0 V

O

V

= 3.3 V

O

V

= 3.3 V

O

V

= 1.8 V

O

10

8

V

O

= 2.5 V

V = 5.0 V

O

V

O

= 1.2 V

V

= 3.3 V

O

6

4

V

= 1.2 V

V

= 1.8 V

O

V

6

= 1.2 V

O

2

0

V

= 1.8 V

V = 12 V

I

V

O

= 2.5 V

2

V = 12 V

I

O

V = 12 V

I

0

2

4

6

8

10

0

2

4

6

8

10

0

4

8

10

I

O

− Output Current − A

I

O

− Output Current − A

I

− Output Current − A

O

Figure 1.

Figure 2.

Figure 3.

SAFE OPERATING AREA

90

80

400 LFM

Natural

Convection

70

60

50

200 LFM

100 LFM

40

30

20

V = 12 V

O

I

V

= 3.3 V

0

2

4

6

8

10

I

O

− Output Current − A

Figure 4.

(1) The electrical characteristic data has been developed from actual products tested at 25°C. This data is considered typical for the

converter. Applies to Figure 1, Figure 2, and Figure 3.

(2) The temperature derating curves represent the conditions at which internal components are at or below the manufacturer's maximum

operating temperatures. Derating limits apply to modules soldered directly to a 100 mm x 100 mm double-sided PCB with 2 oz. copper.

For surface mount packages (AS and AZ suffix), multiple vias must be utilized. Please refer to the mechanical specification for more

information. Applies to Figure 4.

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(1)(2)

TYPICAL CHARACTERISTICS

CHARACTERISTIC DATA ( V_I= 5 V)

EFFICIENCY

vs

LOAD CURRENT

OUTPUT RIPPLE

vs

LOAD CURRENT

POWER DISSIPATION

vs

LOAD CURRENT

10

2.5

100

90

V

O

= 3.3 V

V

O

= 3.3 V

V = 5 V

I

V

O

= 1.8 V

2.0

1.5

8

6

V

O

= 2.5 V

80

V

O

= 0.69 V

V

= 2.5 V

O

V

O

= 1.2 V

V

O

= 3.3 V

70

60

V

= 0.9 V

V

V = 0.9 V

O

V

O

= 1.2 V

V = 1.8 V

O

V

O

= 1.2 V

1.0

0.5

4

2

= 1.8 V

V

O

= 0.69 V

O

50

V

O

= 0.69 V

40

30

V

O

= 2.5 V

2

V

= 0.9 V

O

V = 5 V

I

V = 5 V

I

0

2

4

6

8

10

0

2

4

6

8

10

0

4

6

8

10

I

O

− Output Current − A

I

O

− Output Current − A

I

O

− Output Current − A

Figure 5.

Figure 6.

Figure 7.

SAFE OPERATING AREA

90

80

Natural

Convection

70

60

50

40

30

20

V = 5 V

O

I

V

= 3.3 V

0

2

4

6

8

10

I

O

− Output Current − A

Figure 8.

(1) The electrical characteristic data has been developed from actual products tested at 25°C. This data is considered typical for the

converter. Applies to Figure 5, Figure 6, and Figure 7.

(2) The temperature derating curves represent the conditions at which internal components are at or below the manufacturer's maximum

operating temperatures. Derating limits apply to modules soldered directly to a 100 mm x 100 mm double-sided PCB with 2 oz. copper.

For surface mount packages (AS and AZ suffix), multiple vias must be utilized. Please refer to the mechanical specification for more

information. Applies to Figure 8.

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APPLICATION INFORMATION

CAPACITOR RECOMMENDATIONS FOR THE PTH08T240W POWER MODULE

Input Capacitor (Required)

The required input capacitance is 220-µF of electrolytic type. When V_O> 3V , the 220 µF electrolytic capacitor

must be rated for 700 mArms ripple current capability. For V_O≤ 3 V, the ripple current rating must be at least 450

mArms. The size, type and value of input capacitor is determined by the converter’s transient performance

capability. This minimum value assumes that the converter is supplied with a responsive, low inductance input

source. This source should have ample capacitive decoupling, and be distributed to the converter via PCB power

and ground planes.

For high-performance applications, or wherever the input source performance is degraded, 470 µF of input

capacitance is recommended. The additional input capacitance above the minimum level insures an optimized

performance.

Ripple current (rms) rating, less than 100 mΩ of equivalent series resistance (ESR), and temperature are the

main considerations when selecting input capacitors. The ripple current reflected from the input of the

PTH08T240W module is moderate to low. Therefore any good quality, computer-grade electrolytic capacitor will

have an adequate ripple current rating.

Regular tantalum capacitors are not recommended for the input bus. These capacitors require a recommended

minimum voltage rating of 2 × (maximum dc voltage + ac ripple). This is standard practice to ensure reliability. No

tantalum capacitors were found with a sufficient voltage rating to meet this requirement. When the operating

temperature is below 0°C, the ESR of aluminum electrolytic capacitors increases. For these applications,

Os-Con, poly-aluminum, and polymer-tantalum types should be considered. Adding one or two ceramic

capacitors to the input attenuates high-frequency reflected ripple current.

TurboTrans Output Capacitor

The PTH08T240W requires a minimum output capacitance of 220 µF. The required capacitance above 220 µF

will be determined by actual transient deviation requirements.

TurboTrans allows the designer to optimize the capacitance load according to the system transient design

requirement. High quality, ultra-low ESR capacitors are required to maximize TurboTrans effectiveness.

Capacitors with a capacitance (µF) × ESR (mΩ) product of ≤ 10,000 mΩ×µF are required.

Working Example:

A bank of 6 identical capacitors, each with a capacitance of 330 µF and 5 mΩ ESR, has a C × ESR product of

1650 µFxmΩ (330 µF × 5 mΩ).

Using TurboTrans in conjunction with the high quality capacitors (capacitance (µF) × ESR (mΩ)) reduces the

overall capacitance requirement while meeting the minimum transient amplitude level.

Table 1 includes a preferred list of capacitors by type and vendor. See the Output Bus / TurboTrans column.

Note: See the TurboTrans Technology Application Notes within this document for selection of specific

capacitance.

Non-TurboTrans Output Capacitor

The PTH08T240W requires a minimum output capacitance of 220 µF. Non-TurboTrans applications must

observe minimum output capacitance ESR limits.

A combination of 200 µF of ceramic capacitors plus low ESR (15 mΩ to 30 mΩ) Os-Con electrolytic/tantalum

type capacitors can be used. When using Polymer tantalum types, tantalum type, or Oscon types only, the

capacitor ESR bank limit is 3 mΩ to 5 mΩ. (Note: no ceramic capacitors are required). This is necessary for the

stable operation of the regulator. Additional capacitance can be added to improve the module's performance to

load transients. High quality computer-grade electrolytic capacitors are recommended. Aluminum electrolytic

capacitors provide adequate decoupling over the frequency range, 2 kHz to 150 kHz, and are suitable when

ambient temperatures are above -20°C. For operation below -20°C, tantalum, ceramic, or Os-Con type

capacitors are necessary.

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APPLICATION INFORMATION (continued)

When using a combination of one or more non-ceramic capacitors, the calculated equivalent ESR should be no

lower than 2 mΩ (4 mΩ when calculating using the manufacturer’s maximum ESR values). A list of preferred

low-ESR type capacitors, are identified in Table 1.

Ceramic Capacitors

Above 150 kHz the performance of aluminum electrolytic capacitors is less effective. Multilayer ceramic

capacitors have very low ESR and a resonant frequency higher than the bandwidth of the regulator. They can be

used to reduce the reflected ripple current at the input as well as improve the transient response of the output.

When used on the output their combined ESR is not critical as long as the total value of ceramic capacitors, with

values between 10 µF and 100 µF, does not exceed 3000 µF (non-TurboTrans). In TurboTrans applications,

when ceramic capacitors are used on the output bus, total capacitance including bulk and ceramic types is not to

exceed 14,000 µF.

Tantalum, Polymer-Tantalum Capacitors

Tantalum type capacitors are only used on the output bus, and are recommended for applications where the

ambient operating temperature is less than 0°C. The AVX TPS series and Kemet capacitor series are suggested

over many other tantalum types due to their higher rated surge, power dissipation, and ripple current capability.

As a caution, many general-purpose tantalum capacitors have higher ESR, reduced power dissipation, and lower

ripple current capability. These capacitors are also less reliable due to their reduced power dissipation and surge

current ratings. Tantalum capacitors that have no stated ESR or surge current rating are not recommended for

power applications.

Capacitor Table

Table 1 identifies the characteristics of capacitors from a number of vendors with acceptable ESR and ripple

current (rms) ratings. The recommended number of capacitors required at both the input and output buses is

identified for each capacitor type.

This is not an extensive capacitor list. Capacitors from other vendors are available with comparable

specifications. Those listed are for guidance. The RMS ripple current rating and ESR (at 100 kHz) are critical

parameters necessary to ensure both optimum regulator performance and long capacitor life.

Designing for Fast Load Transients

The transient response of the dc/dc converter has been characterized using a load transient with a di/dt of

2.5 A/µs. The typical voltage deviation for this load transient is given in the Electrical Characteristics table using

the minimum required value of output capacitance. As the di/dt of a transient is increased, the response of a

converter’s regulation circuit ultimately depends on its output capacitor decoupling network. This is an inherent

limitation with any dc/dc converter once the speed of the transient exceeds its bandwidth capability.

If the target application specifies a higher di/dt or lower voltage deviation, the requirement can only be met with

additional low ESR ceramic capacitor decoupling. Generally, with 50% load steps at > 100 A/µs, adding multiple

10 µF ceramic capacitors, 3225 case size, plus 10 × 1 µF, including numerous high frequency ceramics

(≤ 0.1 µF) are all that is required to soften the transient higher frequency edges. Special attention is essential

with regards to location, types, and position of higher frequency ceramic and lower ESR bulk capacitors. DSP,

FPGA and ASIC vendors identify types, location and capacitance required for optimum performance of the high

frequency devices. The details regarding the PCB layout and capacitor/component placement are important at

these high frequencies. Low impedance buses and unbroken PCB copper planes with components located as

close to the high frequency processor are essential for optimizing transient performance. In many instances

additional capacitors may be required to insure and minimize transient aberrations.

9

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APPLICATION INFORMATION (continued)

Table 1. Input/Output Capacitors⁽¹⁾

Capacitor Characteristics

Quantity

Output Bus

Max

Ripple

Current at

85°C

Max.

ESR

at 100

kHz

Capacitor Vendor,

Type Series (Style)

Working Value

Physical

Size (mm)

Input

Bus

TurboTrans

Vendor Part No.

No

Voltage

(µF)

(Cap

TurboTrans

Type)⁽²⁾

(Irms)

Panasonic (Radial)

FC (Radial)

25 V

270 0.090Ω

>755mA

10 × 12,5

12,5 × 15

≥1⁽³⁾

≥ 1⁽⁴⁾

N/R⁽⁵⁾

EEUFC1E271

560 0.065Ω 1205 mA

470 0.065Ω >1200 mA

EEUFC1E561S

EEVFC1E471LQ

FC(SMD)

12,5 ×

16,5

FK(SMD)

25 V

470 0.080Ω

850 mA

10 ×10,2

≥1⁽³⁾

≥ 1⁽⁶⁾

N/R⁽⁵⁾

EEVFK1E471P

United Chemi-Con

PTB(SMD) Polymer

Tantalum

6.3 V

330 0.025Ω 2600 mA

330 0.09Ω 760 mA

7,3x 4,3x N/R⁽⁷⁾⁽⁸

≥ 1 ~ ≤ 4⁽⁴⁾

C ≥ 2⁽²⁾

4PTB337MD6TER

)

2.8

(V_I:V_O≥5.1V)⁽⁷⁾

(4)

LXZ, Aluminum (Radial)

25 V

16 V

10 × 12,5

≥1⁽³⁾

≥ 1

N/R⁽⁵⁾

LXZ25VB331M10X12LL

16PS330MJ12

PS,

330 0.014Ω 5060 mA

330 0.014Ω 5050 mA

270 0.014Ω 4420 mA

330 0.014Ω 4420 mA

≥ 1 ~ ≤ 3

≥ 1 ~≤ 2

≥ 1 ~ ≤ 2

B ≥ 2⁽²⁾

Poly-Aluminum(Radial)

PXA, Poly-Aluminum

(SMD)

16 V

10 V

10 × 12,2

8 × 11,5

8 × 12

≥1⁽³⁾

B ≥ 2⁽²⁾

PXA16VC331MJ12TP

PS,

N/R⁽⁷⁾⁽⁸

10PS270MH11(V_I:V_O≥5.5V)⁽⁷⁾

)

Poly-Aluminum(Radial)

PXA,

N/R⁽⁷⁾⁽⁸

PXA10VC331MH12

)

Poly-Aluminum(Radial)

(V_I:V_O≥5.5V)⁽⁷⁾

Nichicon, Aluminum

HD (Radial)

25 V

35 V

330 0.095Ω

220 0.072Ω

750 mA

760 mA

10 × 15

8 × 11,5

16 × 15

≥1⁽³⁾

≥ 1⁽⁴⁾

≥ 2⁽⁴⁾

N/R⁽⁵⁾

UPM1E331MPH6

UHD1E221MPR

UPM1V561MHH6

PM (Radial)

560 0.048Ω 1360 mA

Panasonic,

Poly-Aluminum:

7,3 L×4,3 N/R⁽⁷⁾⁽⁸

)

2.0 V

390 0.005Ω 4000 mA

W ×4,2H

N/R⁽⁸⁾

B ≥ 2⁽²⁾

EEFSE0J391R(V_O≤1.6V)⁽⁹⁾

(1) Capacitor Supplier Verification

Please verify availability of capacitors identified in this table. Capacitor suppliers may recommend alternative part numbers because of

limited availability or obsolete products. In some instances, the capacitor product life cycle may be in decline and have short-term

consideration for obsolescence.

RoHS, Lead-free and Material Details

See the capacitor suppliers regarding material composition, RoHS status, lead-free status, and manufacturing process requirements.

Component designators or part number deviations can occur when material composition or soldering requirements are updated.

(2) Required capacitors with TurboTrans. See the TransTrans Application information for Capacitor Selection

Capacitor Type Groups by ESR (Equivalent Series Resistance) :

•

Type A = (100 < capacitance × ESR ≤ 1000)

Type B = (1,000 < capacitance × ESR ≤ 5,000)

Type C = (5,001 < capacitance × ESR ≤ 10,000)

(3) In addition to the required input electrolytic capacitance , ≥ 20 µF ceramic capacitors are required to reduce the high-frequency reflected

ripple current.

(4) Total bulk nonceramic capacitors on the output bus with ESR of ≥ 15mΩ to ≤ 30mΩ requires an additional ≥ 200 µF of ceramic

capacitor.

(5) Aluminum Electrolytic capacitor not recommended for the TurboTrans due to higher ESR × capacitance products. Aluminum and higher

ESR capacitors can be used in conjunction with lower ESR capacitance.

(6) Output bulk capacitor's maximum ESR is ≥ 30 mΩ. Additional ceramic capacitance of ≥ 200 µF is required.

(7) The voltage rating and derating of this capacitor only allows it to be used for voltages that are equal or less than 5.1 V.

(8) N/R – Not recommended. The voltage rating does not meet the minimum operating limits.

(9) The voltage rating of this capacitor only allows it to be used for output voltage that is equal to or less than 80% of the working voltage.

10

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APPLICATION INFORMATION (continued)

Table 1. Input/Output Capacitors (continued)

Capacitor Characteristics

Quantity

Output Bus

Max

Max.

Capacitor Vendor,

Type Series (Style)

Ripple

Working Value

ESR

at 100

kHz

Physical

Size (mm)

Input

Bus

TurboTrans

(Cap

Current at

85°C

(Irms)

Vendor Part No.

No

Voltage

(µF)

TurboTrans

Type)⁽²⁾

Sanyo

TPE, Poscap (SMD)

10 V

330 0.025Ω 3000 mA

7,3 × 4,3 N/R⁽¹⁰⁾⁽

≥ 1 ~ ≤ 3

C ≥ 2⁽¹²⁾

10TPE330MF (V_I:V_O≤ 5.1 V)⁽¹³⁾

11)

TPE Poscap(SMD)

TPD Poscap (SMD)

SEP, Os-Con (Radial)

SP Oscon ( Radial)

SEPC, Os-Con (Radial)

SVP, Os-Con (SMD)

2.5 V

16 V

470 0.007Ω 4400 mA

1000 0.005Ω 6100 mA

330 0.016Ω >4700 mA

7,3 × 4,3

10 ×13

N/R⁽¹¹⁾

≥1⁽¹⁴⁾

≥ 1 ≤ 2

≤ 1

B ≥ 2⁽¹²⁾

B ≥ 1⁽¹²⁾

B ≥ 2⁽¹²⁾

2R5TPE470M7(V_O≤ 1.8 V)⁽¹³⁾

2R5TPD1000M5(V_O≤ 1.8 V)⁽¹³⁾

16SEP330M

≥ 1 ~ ≤ 3

≥ 1 ~ ≤ 2

≥ 1 ~ ≤ 3⁽¹⁵⁾

270

270 0.011Ω >5000 mA

330 0.016Ω 4700mA

0.018 >4400 mA 10 × 11,5

16SP270M

8 × 13

16SEPC270M

10 × 12,6

B ≥ 2^(12)(15)16SVP330M

AVX, Tantalum, Series III

TPM Multianode

10 V

330 0.040Ω >1828 mA 7,3L×4,3W N/R⁽¹¹⁾

≥ 1 ~ ≤ 6⁽¹⁵⁾

≥ 1 ~ ≤ 3⁽¹⁵⁾

N/R⁽¹⁶⁾

TPSE337M010R0040(V_O≥5V)⁽¹⁰⁾

330 0.023Ω >3000 mA

× 4,1 H

N/R⁽¹¹⁾

C ≥ 2^(12)(15)TPME337M010#0023(V_O≥5V)⁽¹⁰⁾

TPS Series III (SMD)

Kemet, Poly-Tantalum

T520 (SMD)

4 V

10 V

6.3 V

4 V

1000 0.035Ω 2405

7,3L ×

5,7W

≥ 1 ~ ≤ 5⁽¹⁵⁾

≥ 1~ ≤ 4⁽¹⁵⁾

≥ 2 ~ ≤ 3

≤ 1

N/R⁽¹⁶⁾

C ≥ 2⁽¹²⁾

B ≥ 2⁽¹²⁾

B ≥ 1⁽¹²⁾

TPSV108K004R0035 (V_O≤ 2.1

V)⁽¹³⁾

330 0.025Ω 2600 mA

330 0.015Ω >3800 mA

680 0.005Ω 7300 mA

1000 0.005Ω 7300 mA

4,3 W

× 7,3 L

× 4 H

N/R⁽¹¹⁾

T520X337M010ASE025

(V_I:V_O≥5.5V)⁽¹⁰⁾

N/R⁽¹⁰⁾⁽

T530X337M006ASE015

11)

(V_I:V_O≥5.1V)⁽¹⁰⁾

T530 (SMD)

N/R⁽¹¹⁾

T530X687M004ASE005 (V_O

3.5 V)⁽¹³⁾

≤

T530 (SMD)

2.5 V

4,3 w ×

7,3 L

≤ 1

T530X108M2R5ASE005 (V_O

2.0 V)⁽¹³⁾

≤

Vishay-Sprague

597D, Tantalum (SMD)

16 V

220

0.04Ω

2300 mA 7,2L×5,7W N/R⁽¹¹⁾

×4,1H

≥ 1 ~ ≤ 5

C ≥ 2⁽¹²⁾

597D227X16E2T (V_I:V_O≥5.5V)⁽¹⁰⁾

94SP, Os-con (Radial)

94SVP Os-Con(SMD)

Kemet, Ceramic X5R

(SMD)

16 V

6.3 V

25 V

16 V

6.3 V

16 V

270 0.018Ω

4400mA

10 × 10,5

≥1⁽¹⁴⁾

≥ 1 ~ ≤ 3

≥ 1⁽¹⁷⁾

C ≥ 2⁽¹²⁾

B ≥ 2⁽¹²⁾

A⁽¹²⁾

94SP277X0016FBP

94SVP337X016F12

C1210C106M4PAC

C1210C476K9PAC

GRM32ER60J107M

GRM32ER60J476M

GRM32ER61E226K

GRM32DR61C106K

C3225X5R0J107MT

C3225X5R0J476MT

C3225X5R1C106MT0

C3225X5R1C226MT

330 0.017Ω >4500 mA 10 × 12,7

10

47

0.002Ω

–

3225

≥2⁽¹⁴⁾

N/R⁽¹¹⁾

≥ 1⁽¹⁴⁾

≥2⁽¹⁴⁾

A⁽¹²⁾

Murata, Ceramic X5R

(SMD)

100 0.002Ω

A⁽¹²⁾

47

A⁽¹²⁾

22

A⁽¹²⁾

10

A⁽¹²⁾

TDK, Ceramic X5R

(SMD)

100 0.002Ω

–

3225

N/R⁽¹¹⁾

≥2⁽¹⁴⁾

A⁽¹²⁾

47

10

22

A⁽¹²⁾

≥1⁽¹⁴⁾

A⁽¹²⁾

(10) The voltage rating and derating of this capacitor only allows it to be used for voltages that are equal or less than 5.1 V.

(11) N/R – Not recommended. The voltage rating does not meet the minimum operating limits.

(12) Required capacitors with TurboTrans. See the TransTrans Application information for Capacitor Selection

Capacitor Type Groups by ESR (Equivalent Series Resistance) :

•

Type A = (100 < capacitance × ESR ≤ 1000)

Type B = (1,000 < capacitance × ESR ≤ 5,000)

Type C = (5,001 < capacitance × ESR ≤ 10,000)

(13) The voltage rating of this capacitor only allows it to be used for output voltage that is equal to or less than 80% of the working voltage.

(14) In addition to the required input electrolytic capacitance , ≥ 20 µF ceramic capacitors are required to reduce the high-frequency reflected

ripple current.

(15) Total bulk nonceramic capacitors on the output bus with ESR of ≥ 15mΩ to ≤ 30mΩ requires an additional ≥ 200 µF of ceramic

capacitor.

(16) Aluminum Electrolytic capacitor not recommended for the TurboTrans due to higher ESR × capacitance products. Aluminum and higher

ESR capacitors can be used in conjunction with lower ESR capacitance.

(17) Maximum ceramic capacitance on the output bus is ≤ tbd µF. Any combination of the ceramic capacitor values is limited to tbd µF for

non-TurboTrans applications. The total capacitance is limited to tbd µF which includes all ceramic and non-ceramic types.

11

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TurboTrans™ Technology

TurboTrans technology is a feature introduced in the T2 generation of the PTH/PTV family of power modules.

TurboTrans optimizes the transient response of the regulator with added external capacitance using a single

external resistor. Benefits of this technology include reduced output capacitance, minimized output voltage

deviation following a load transient, and enhanced stability when using ultra-low ESR output capacitors. The

amount of output capacitance required to meet a target output voltage deviation will be reduced with TurboTrans

activated. Likewise, for a given amount of output capacitance, with TurboTrans engaged, the amplitude of the

voltage deviation following a load transient will be reduced. Applications requiring tight transient voltage

tolerances and minimized capacitor footprint area will benefit greatly from this technology.

TurboTrans™ Selection

Utilizing TurboTrans requires connecting a resistor, R_TT, between the +Sense pin (pin 6) and the TurboTrans pin

(pin 9). The value of the resistor directly corresponds to the amount of output capacitance required. All T2

products require a minimum value of output capacitance whether or not TurboTrans is utilized. For the

PTH08T240W, the minimum required capacitance is 220 µF. When using TurboTrans, capacitors with a

capacitance × ESR product below 10,000 µF×mΩ are required. (Multiply the capacitance (in µF) by the ESR (in

mΩ) to determine the capacitance × ESR product.) See the Capacitor Selection section of the datasheet for a

variety of capacitors that meet this criteria.

Figure 9 thru Figure 13 show the amount of output capacitance required to meet a desired transient voltage

deviation with and without TurboTrans for several capacitor types; Type A (e.g. ceramic), Type B (e.g.

polymer-tantalum), and Type C (e.g. OS-CON). To calculate the proper value of R_TT, first determine your

required transient voltage deviation limits and magnitude of your transient load step. Next, determine what type

of output capacitors will be used. (If more than one type of output capacitor is used, select the capacitor type that

makes up the majority of your total output capacitance.) Knowing this information, use the chart in Figure 9 thru

Figure 13 that corresponds to the capacitor type selected. To use the chart, begin by dividing the maximum

voltage deviation limit (in mV) by the magnitude of your load step (in Amps). This gives a mV/A value. Find this

value on the Y-axis of the appropriate chart. Read across the graph to the 'With TurboTrans' plot. From this

point, read down to the X-axis which lists the minimum required capacitance, C_O, to meet that transient voltage

deviation. The required R_TTresistor value can then be calculated using the equation or selected from the

TurboTrans table. The TurboTrans tables include both the required output capacitance and the corresponding

R_TTvalues to meet several values of transient voltage deviation for 25% (2.5 A), 50% (5 A), and 75% (7.5 A)

output load steps.

The chart can also be used to determine the achievable transient voltage deviation for a given amount of output

capacitance. By selecting the amount of output capacitance along the X-axis, reading up to the desired 'With

TurboTrans'' curve, and then over to the Y-axis, gives the transient voltage deviation limit for that value of output

capacitance. The required R_TTresistor value can be calculated using the equation or selected from the

TurboTrans table.

As an example, let's look at a 12-V application requiring a 50 mV deviation during an 5 A, 50% load transient. A

majority of 330 µF, 10 mA ouput capacitors will be used. Use the 12-V, Type B capacitor chart, Figure 10.

Dividing 50 mV by 5 A gives 10 mV/A transient voltage deviation per amp of transient load step. Select 10 mV/A

on the Y-axis and read across to the 'With TurboTrans'' plot. Following this point down to the X-axis gives a

minimum required output capacitance of approximately 680 µF. The required R_TTresistor value for 680 µF can

then be calculated or selected from Table 3. The required R_TTresistor is approximately 7.32 kΩ.

To see the benefit of TurboTrans, follow the 10 mV/A marking across to the 'Without TurboTrans' plot. Following

that point down shows that you would need a minimum of 3000 µF of output capacitance to meet the same

transient deviation limit. This is the benefit of TurboTrans.

12

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6

5

4

3

2

1

C - Capacitance - mF

Figure 9. Capacitor Type A, 100 ≤ C(µF)xESR(mΩ) ≤ 1000

(e.g. Ceramic)

Table 2. Type A TurboTrans C_OValues and Required R_TTSelection Table

Transient Voltage Deviation (mV)

C_O

R_TT

Minimum Required Output

Capacitance (µF)

Required TurboTrans

Resistor (Ω)

25% load step

(2.5 A)

50% load step

(5 A)

75% load step

(7.5 A)

tbd

open

tbd

short

R_TTResistor Selection

The TurboTrans resistor value, R_TTcan be determined from the TurboTrans programming, see Equation 1

R

+ TBD

TT

(1)

Where C_Ois the total output capacitance in µF. C_Ovalues greater than or equal to TBD µF require R_TTto be a

short, 0Ω.

To ensure stability, a minimum amount of output capacitance is required for a given R_TTresistor value. The value

of R_TTmust be calculated using the minimum required output capacitance determined from the capacitor

transient response charts above.

13

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Type B Capacitor

12-V Input

Type B Capacitor

5-V Input

30

20

WIth TurboTrans

Without TurboTrans

WIth TurboTrans

Without TurboTrans

20

10

9

8

7

10

9

8

7

6

5

6

5

4

3

4

3

2

I

O

− Output Current − A

C − Capacitance − µF

Figure 10. Cap Type B, 1000 < C(µF)xESR(mΩ) ≤ 5000

Figure 11. Cap Type B, 1000 < C(µF)xESR(mΩ) ≤ 5000

(e.g. Polymer-Tantalum)

Table 3. Type B TurboTrans C_OValues and Required R_TTSelection Table

Transient Voltage Deviation (mV)

12-V Input

5-V Input

25% load step

(2.5 A)

50% load step

(5 A)

75% load step

(7.5 A)

C_O

R_TT

C_O

R_TT

Minimum

Required

Minimum

Required

Required Output

Capacitance (µF)

TurboTrans

Resistor (kΩ)

Required Output

Capacitance (µF)

TurboTrans

Resistor (kΩ)

55

40

35

30

25

20

15

10

110

80

70

60

50

40

30

20

165

120

105

90

220

330

open

57.6

30.9

16.2

7.32

1.58

short

220

360

open

42.2

23.7

12.7

5.49

0.536

short

—

400

450

510

560

75

680

750

60

1000

2100

10500

1050

45

2600

30

exceeds limit

R_TTResistor Selection

The TurboTrans resistor value, R_TTcan be determined from the TurboTrans programming, see Equation 2. For

_TTvalues.

^{V > 3.3 V please}ƪ^{contact TI for C and R}

_{40 1 *}ǒ_{C ń1100}Ǔƫ

O

ƪǒ_{C ń220}Ǔ^O_* 1

ƫ

(

)

kW

R

+

For V v 3.3 V, C

+ 220 mF

TT

O

O(min)

O

(2)

Where C_Ois the total output capacitance in µF. C_Ovalues greater than or equal to 1100 µF require R_TTto be a

short, 0Ω. (R_TTresults in a negative value when C_O> 1100 µF).

To ensure stability, a minimum amount of output capacitance is required for a given R_TTresistor value. The value

of R_TTmust be calculated using the minimum required output capacitance determined from the capacitor

transient response charts above.

14

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Type C Capacitor

12-V Input

Type C Capacitor

5-V Input

30

20

30

20

WIth TurboTrans

Without TurboTrans

WIth TurboTrans

Without TurboTrans

10

9

8

7

10

9

8

7

6

5

6

5

4

3

4

3

2

I

O

− Output Current − A

C − Capacitance − µF

Figure 12. Cap Type C, 5000 < C(µF)xESR(mΩ) ≤ 10,000

Figure 13. Cap Type C, 5000 < C(µF)xESR(mΩ) ≤ 10,000

(e.g. Os-Con)

Table 4. Type C TurboTrans C_OValues and Required R_TTSelection Table

Transient Voltage Deviation (mV)

12-V Input

5-V Input

25% load step

(2.5 A)

50% load step

(5 A)

75% load step

(7.5 A)

C_O

R_TT

C_O

R_TT

Minimum

Required

Minimum

Required

Required Output

Capacitance (µF)

TurboTrans

Resistor (kΩ)

Required Output

Capacitance (µF)

TurboTrans

Resistor (kΩ)

75

60

45

35

30

25

20

15

10

150

120

90

225

180

135

105

90

220

270

open

294

250

330

1300

133

400

68.1

31.6

20.0

11.8

5.23

short

480

45.3

21.5

13.7

7.68

2.61

short

—

70

580

700

60

720

860

50

75

950

1150

40

60

1300

2000

7400

1550

30

45

2800

20

30

exceeds limit

R_TTResistor Selection

The TurboTrans resistor value, R_TTcan be determined from the TurboTrans programming, see Equation 3 . For

V_O> 3.3 V please contact TI for C_Oand R_TTvalues.

ƪ

ǒ

Ǔƫ

40 1 * C ń1980

O

(

)

kW

R

+

For V v 3.3 V

TT

O

ǒ

Ǔ _{) 880 ń1980 * 1}

Ǔ

ǒ

ƪ

Ǔ

ƫ

5 C

O

(3)

Where C_Ois the total output capacitance in µF. C_Ovalues greater than or equal to 1980 µF require R_TTto be a

short, 0Ω. (R_TTresults in a negative value when C_O> 1980 µF).

To ensure stability, the value of R_TTmust be calculated using the minimum required output capacitance

determined from the capacitor transient response charts above.

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TurboTrans

R

TT

0 kW

10

AutoTrack

Smart

9

TurboTrans

+Sense

6

1

2

+Sense

Sync

V

I

V

O

5

7

PTH08T240W

V

I

V

O

11

Inhibit/

Prog UVLO

−Sense

V Adj

O

GND

3

4

8

L

O

A

D

C

OTT

C

I

1320 mF

Type B

(Required)

220 mF

(Required)

R

SET

1%

0.05 W

−Sense

GND

Figure 14. TurboTrans™ with Minimum Capacitance Requirement

Without TurboTrans

100 mV/div

With TurboTrans

100 mV/div

2.5 A/ms

50% Load Step

Figure 15. TurboTrans Waveform

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ADJUSTING THE OUTPUT VOLTAGE OF THE PTH08T240W WIDE-OUTPUT ADJUST POWER

MODULE

The V_oAdjust control (pin 8) sets the output voltage of the PTH08T240W. The adjustment range of the

PTH08T240W is 0.69 V to 5.5 V. The adjustment method requires the addition of a single external resistor, R_SET

,

that must be connected directly between the V_oAdjust and – Sense pins. Table 5 gives the standard value of the

external resistor for a number of standard voltages, along with the actual output voltage that this resistance value

provides.

For other output voltages, the value of the required resistor can either be calculated using the following formula,

or simply selected from the range of values given in Table 6. Figure 16 shows the placement of the required

resistor.

R

0.69

= 10 kW x

- 1.43 kW

SET

V

- 0.69

O

(4)

Table 5. Standard Values of R_SETfor Standard Output Voltages

V_O(Standard)

R_SET(Standard Value)

169 Ω

V_O(Actual)

5.01 V

(1)

5.0 V

3.3 V

2.5 V

1.8 V

1.5 V

1.21 kΩ

3.30 V

2.37 kΩ

2.51 V

4.75 kΩ

1.81 V

7.15 kΩ

1.49 V

(2)

1.2 V

12.1 kΩ

1.20 V

(2)

1 V

20.5 kΩ

1.00 V

(2)

0.7 V

681 kΩ

0.700 V

(1) The minimum input voltage is (V_O+ 2) V.

(2) The maximum input voltage is (V_O× 11) or 14 V, whichever is less. The maximum allowable input

voltage is a function of switching frequency and may increase or decrease when the Smart Sync

feature is utilized. Please review the Smart Sync application section for further guidance.

+Sense

6

+Sense

V

O

5

7

PTH08T240W

V

O

−Sense

V Adj

O

GND

3

4

8

C

O

R

SET

1%

0.05 W

−Sense

GND

(1)

(2)

Use a 0.05 W resistor. The tolerance should be 1%, with temperature stability of 100 ppm/°C (or better). Place the

resistor as close to the regulator as possible. Connect the resistor directly between pins 8 and 7 using dedicated PCB

traces.

Never connect capacitors from V_OAdjust to either + Sense, GND, or V_O. Any capacitance added to the V_OAdjust

pin affects the stability of the regulator.

Figure 16. V_oAdjust Resistor Placement

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Table 6. Output Voltage Set-Point Resistor Values

V_ORequired

R_SET

V_ORequired

1.950

R_SET

4.05 kΩ

3.46 kΩ

2.99 kΩ

2.61 kΩ

2.38 kΩ

2.00 kΩ

1.76 kΩ

1.56 kΩ

1.38 kΩ

1.21 kΩ

1.07 kΩ

941 Ω

825 Ω

720 Ω

593 Ω

536 Ω

455 Ω

381 Ω

312 Ω

249 Ω

171 Ω

135 Ω

83 Ω

(1)

0.700

681 kΩ

113 kΩ

61.3 kΩ

41.7 kΩ

31.4 kΩ

25.1 kΩ

20.8 kΩ

17.8 kΩ

15.4 kΩ

13.6 kΩ

12.1 kΩ

10.9 kΩ

9.88 kΩ

9.03 kΩ

8.29 kΩ

7.65 kΩ

7.09 kΩ

6.59 kΩ

6.15 kΩ

5.76 kΩ

5.40 kΩ

5.08 kΩ

4.78 kΩ

4.52 kΩ

4.27 kΩ

(1)

0.750

2.100

(1)

0.800

2.250

(1)

0.850

2.400

(1)

0.900

2.500

(1)

0.950

2.700

(1)

1.000

2.850

(1)

1.050

3.000

(1)

1.100

3.150

(1)

1.150

3.300

(1)

1.200

3.450

1.250

1.300

1.350

1.400

1.450

1.500

1.550

1.600

1.650

1.700

1.750

1.800

1.850

1.900

3.600

(2)

3.750

(2)

3.900

(2)

4.100

(2)

4.200

(2)

4.350

(2)

4.500

(2)

4.650

(2)

4.800

(2)

5.000

(2)

5.100

(2)

5.250

(2)

5.400

35 Ω

(2)

5.500

5 Ω

(1) The maximum input voltage is (V_O× 11) or 14 V, whichever is less. The maximum allowable input

voltage is a function of switching frequency and may increase or decrease when the Smart Sync

feature is utilized. Please review the Smart Sync application section for further guidance.

(2) For V_O> 3.6 V, the minimum input voltage is (V_O+ 2) V.

ADJUSTING THE UNDERVOLTAGE LOCKOUT (UVLO) OF THE PTH08T240W POWER MODULES

The PTH08T240W power modules incorporate an input undervoltage lockout (UVLO). The UVLO feature

prevents the operation of the module until there is sufficient input voltage to produce a valid output voltage. This

enables the module to provide a clean, monotonic powerup for the load circuit, and also limits the magnitude of

current drawn from the regulator’s input source during the power-up sequence.

The UVLO characteristic is defined by the ON threshold (V_THD) voltage. Below the ON threshold, the Inhibit

control is overridden, and the module does not produce an output. The hysterisis voltage, which is the difference

between the ON and OFF threshold voltages, is set at 500 mV. The hysterisis prevents start-up oscillations,

which can occur if the input voltage droops slightly when the module begins drawing current from the input

source.

UVLO Adjustment

The UVLO feature of the PTH08T240W module allows for limited adjustment of the ON threshold voltage. The

adjustment is made via the Inhbit/UVLO Prog control pin (pin 11). When pin 11 is left open circuit, the ON

threshold voltage is internally set to its default value, which is 4.3 volts. When the ON threshold is adjusted

higher than 5 volts, the default hysterisis setting is 500 mV. This ensures that the module produces a regulated

output when the minimum input voltage is applied (see specifications).

The ON threshold might need to be raised if the module is powered from a tightly regulated 12-V bus. This

prevents it from operating if the input bus fails to completely rise to its specified regulation voltage.

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V

I

2

PTH08T240W

V

I

Inhibit/

UVLO Prog

11

GND

3

4

R

UVLO

C

I

GND

Figure 17. Undervoltage Lockout Adjustment Resistor Placement

Equation 5 determines the value of R_THDrequired to adjust V_THDto a new value. The default value is 4.3 V, and it

may only be adjusted to a higher value.

ǒ

Ǔ

9690 * 137 V

I

( )

kW

R

+

UVLO

ǒ

_{137 V}Ǔ _* 585

I

(5)

Calculated Values

Table 7 shows a chart of standard resistor values for R_UVLOfor different options of the on-threshold (V_THD

)

voltage. For most applications, only the on-threshold voltage should need to be adjusted. In this case select only

a value for R_UVLOfrom right-hand column.

Table 7. Calculated Values of R_UVLOfor Various Values of V_THD

V_THD

7.0 V

7.5 V

8.0 V

8.5 V

9.0 V

9.5 V

10.0 V

10.5 V

11.0 V

R_UVLO

23.2 kΩ

19.6 kΩ

16.9 kΩ

14.7 kΩ

13.0 kΩ

11.8 kΩ

10.5 kΩ

9.76 kΩ

8.87 kΩ

FEATURES OF THE PTH/PTV FAMILY OF NONISOLATED WIDE OUTPUT ADJUST POWER

MODULES

Soft-Start Power Up

The Auto-Track feature allows the power-up of multiple PTH/PTV modules to be directly controlled from the

Track pin. However in a stand-alone configuration, or when the Auto-Track feature is not being used, the Track

pin should be directly connected to the input voltage, V_I(see Figure 18).

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14

Track

V

I

2

PTH08T240W

V

I

GND

3,4

C

I

GND

Figure 18. Track Pin Connection

When the Track pin is connected to the input voltage the Auto-Track function is permanently disengaged. This

allows the module to power up entirely under the control of its internal soft-start circuitry. When power up is

under soft-start control, the output voltage rises to the set-point at a quicker and more linear rate.

From the moment a valid input voltage is applied, the soft-start control introduces a short time delay (typically

2 ms–10 ms) before allowing the output voltage to rise.

V (5 V/div)

I

V

(2 V/div)

O

I (2 A/div)

I

t − Time − 4 ms/div

Figure 19. Power-Up Waveform

The output then progressively rises to the module’s setpoint voltage. Figure 19 shows the soft-start power-up

characteristic of the PTH08T240W operating from a 12-V input bus and configured for a 3.3-V output. The

waveforms were measured with a 10-A constant current load and the Auto-Track feature disabled. The initial rise

in input current when the input voltage first starts to rise is the charge current drawn by the input capacitors.

Power-up is complete within 15 ms.

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Overcurrent Protection

For protection against load faults, all modules incorporate output overcurrent protection. Applying a load that

exceeds the regulator's overcurrent threshold causes the regulated output to shut down. Following shutdown, the

module periodically attempts to recover by initiating a soft-start power-up. This is described as a hiccup mode of

operation, whereby the module continues in a cycle of successive shutdown and power up until the load fault is

removed. During this period, the average current flowing into the fault is significantly reduced. Once the fault is

removed, the module automatically recovers and returns to normal operation.

Overtemperature Protection (OTP)

A thermal shutdown mechanism protects the module’s internal circuitry against excessively high temperatures. A

rise in the internal temperature may be the result of a drop in airflow, or a high ambient temperature. If the

internal temperature exceeds the OTP threshold, the module’s Inhibit control is internally pulled low. This turns

the output off. The output voltage drops as the external output capacitors are discharged by the load circuit. The

recovery is automatic, and begins with a soft-start power up. It occurs when the sensed temperature decreases

by about 10°C below the trip point.

The overtemperature protection is a last resort mechanism to prevent thermal stress to the regulator.

Operation at or close to the thermal shutdown temperature is not recommended and reduces the long-term

reliability of the module. Always operate the regulator within the specified safe operating area (SOA) limits for

the worst-case conditions of ambient temperature and airflow.

On/Off Inhibit

For applications requiring output voltage on/off control, the PTH08T240W incorporates an Inhibit control pin. The

inhibit feature can be used wherever there is a requirement for the output voltage from the regulator to be turned

off.

The power modules function normally when the Inhibit pin is left open-circuit, providing a regulated output

whenever a valid source voltage is connected to V_Iwith respect to GND.

Figure 20 shows the typical application of the inhibit function. Note the discrete transistor (Q1). The Inhibit input

has its own internal pull-up. An external pull-up resistor should never be used with the inhibit pin. The input is not

compatible with TTL logic devices. An open-collector (or open-drain) discrete transistor is recommended for

control.

V

I

2, 6

11

V

I

PTH08T240W

Inhibit/

UVLO

GND

3,4

C

I

Q1

BSS 138

1 = Inhibit

GND

Figure 20. On/Off Inhibit Control Circuit

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Turning Q1 on applies a low voltage to the Inhibit control pin and disables the output of the module. If Q1 is then

turned off, the module executes a soft-start power-up sequence. A regulated output voltage is produced within 15

ms. Figure 21 shows the typical rise in both the output voltage and input current, following the turn-off of Q1. The

turn off of Q1 corresponds to the rise in the waveform, Q1 V_DS. The waveforms were measured with a 16-A

constant current load.

V

(2 V/div)

O

I (2 A/div)

I

V

(2 V/div)

INH

t − Time − 4 ms/div

Figure 21. Power-Up Response from Inhibit Control

Remote Sense

Products with this feature incorporate one or two remote sense pins. Remote sensing improves the load

regulation performance of the module by allowing it to compensate for any IR voltage drop between its output

and the load. An IR drop is caused by the high output current flowing through the small amount of pin and trace

resistance.

To use this feature simply connect the Sense pins to the corresponding output voltage node, close to the load

circuit. If a sense pin is left open-circuit, an internal low-value resistor (15-Ω or less) connected between the pin

and the output node, ensures the output remains in regulation.

With the sense pin connected, the difference between the voltage measured directly between the V_Oand GND

pins, and that measured at the Sense pins, is the amount of IR drop being compensated by the regulator. This

should be limited to a maximum of 0.3 V.

The remote sense feature is not designed to compensate for the forward drop of nonlinear or frequency

dependent components that may be placed in series with the converter output. Examples include OR-ing

diodes, filter inductors, ferrite beads, and fuses. When these components are enclosed by the remote sense

connection they are effectively placed inside the regulation control loop, which can adversely affect the

stability of the regulator.

22

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Smart Sync

Smart Sync is a feature that allows multiple power modules to be synchronized to a common frequency. Driving

the Smart Sync pins with an external oscillator set to the desired frequency, synchronizes all connected modules

to the selected frequency. The synchronization frequency can be higher or lower than the nominal switching

frequency of the modules within the range of 240 kHz to 400 kHz (see Electrical Specifications table for

frequency limits). Synchronizing modules powered from the same bus, eliminates beat frequencies reflected back

to the input supply, and also reduces EMI filtering requirements. These are the benefits of Smart Sync. Power

modules can also be synchronized out of phase to minimize source current loading and minimize input

capacitance requirements. Figure 22 shows a standard circuit with two modules syncronized 180° out of phase

using a D flip-flop.

0^o

Track SYNC TT

+Sense

V_I= 5 V

V

I

V_O1

V

O

PTH08T220W

SN74LVC2G74

INH / UVLO

– Sense

Adj

V

GND

O

Vcc

CLR

CLK

PRE

Q

C_o1

C_i1

220 mF

330 mF

R_SET1

f_clock= 2 X f_modules

D

Q

GND

180^o

Track SYNC TT

+Sense

V

I

V_O2

V

O

PTH08T240W

INH / UVLO

– Sense

V

Adj

GND

O

C_i2

C_o2

220 mF

R_SET2

GND

Figure 22. Smart Sync Schematic

23

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The maximum input voltage allowed for proper synchronization is duty cycle limited. When using Smart Sync, the

maximum allowable input voltage varies as a function of output voltage and switching frequency. Operationally,

the maximum input voltage is inversely proportional to switching frequency. Synchronizing to a higher frequency

causes greater restrictions on the input voltage range. For a given switching frequency, Figure 23 shows how the

maximum input voltage varies with output voltage.

For example, for a module operating at 400 kHz and an output voltage of 1.2 V, the maximum input voltage is

10 V. Exceeding the maximum input voltage may cause in an increase in output ripple voltage and increased

output voltage variation.

As shown in Figure 23, input voltages below 6 V can operate down to the minimum output voltage over the entire

synchronization frequency range. See the Electrical Characteristics table for the synchronization frequency range

limits.

INPUT VOLTAGE

vs

OUTPUT VOLTAGE

15

14

13

12

11

f

= 400 kHz

SW

10

9

f

= 350 kHz

SW

8

7

f

= 300 kHz

SW

f

SW

= 240 kHz

6

5

0.7 0.9 1.1 1.3 1.5 1.7 1.9 2.1 2.3 2.5

V

O

− Output Voltage − V

Figure 23.

Auto-Track™ Function

The Auto-Track function is unique to the PTH/PTV family, and is available with all POLA products. Auto-Track

was designed to simplify the amount of circuitry required to make the output voltage from each module power up

and power down in sequence. The sequencing of two or more supply voltages during power up is a common

requirement for complex mixed-signal applications that use dual-voltage VLSI ICs such as the TMS320™ DSP

family, microprocessors, and ASICs.

How Auto-Track™ Works

(1)

Auto-Track works by forcing the module output voltage to follow a voltage presented at the Track control pin

.

This control range is limited to between 0 V and the module set-point voltage. Once the track-pin voltage is

raised above the set-point voltage, the module output remains at its set-point ⁽²⁾. As an example, if the Track pin

of a 2.5-V regulator is at 1 V, the regulated output is 1 V. If the voltage at the Track pin rises to 3 V, the regulated

output does not go higher than 2.5 V.

When under Auto-Track control, the regulated output from the module follows the voltage at its Track pin on a

volt-for-volt basis. By connecting the Track pin of a number of these modules together, the output voltages follow

a common signal during power up and power down. The control signal can be an externally generated master

ramp waveform, or the output voltage from another power supply circuit ⁽³⁾. For convenience, the Track input

incorporates an internal RC-charge circuit. This operates off the module input voltage to produce a suitable rising

waveform at power up.

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Typical Application

The basic implementation of Auto-Track allows for simultaneous voltage sequencing of a number of Auto-Track

compliant modules. Connecting the Track inputs of two or more modules forces their track input to follow the

same collective RC-ramp waveform, and allows their power-up sequence to be coordinated from a common

Track control signal. This can be an open-collector (or open-drain) device, such as a power-up reset voltage

supervisor IC. See U3 in Figure 24.

To coordinate a power-up sequence, the Track control must first be pulled to ground potential. This should be

done at or before input power is applied to the modules. The ground signal should be maintained for at least

20 ms after input power has been applied. This brief period gives the modules time to complete their internal

soft-start initialization ⁽⁴⁾, enabling them to produce an output voltage. A low-cost supply voltage supervisor IC,

that includes a built-in time delay, is an ideal component for automatically controlling the Track inputs at power

up.

Figure 24 shows how the TL7712A supply voltage supervisor IC (U3) can be used to coordinate the sequenced

power up of PTH08T240W modules. The output of the TL7712A supervisor becomes active above an input

voltage of 3.6 V, enabling it to assert a ground signal to the common track control well before the input voltage

has reached the module's undervoltage lockout threshold. The ground signal is maintained until approximately 28

ms after the input voltage has risen above U3's voltage threshold, which is 4.3 V. The 28-ms time period is

controlled by the capacitor C_T. The value of 2.2 µF provides sufficient time delay for the modules to complete

their internal soft-start initialization. The output voltage of each module remains at zero until the track control

voltage is allowed to rise. When U3 removes the ground signal, the track control voltage automatically rises. This

causes the output voltage of each module to rise simultaneously with the other modules, until each reaches its

respective set-point voltage.

Figure 25 shows the output voltage waveforms after input voltage is applied to the circuit. The waveforms, V_O1

and V_O2, represent the output voltages from the two power modules, U1 (3.3 V) and U2 (1.8 V), respectively.

V_TRK, V_O1, and V_O2 are shown rising together to produce the desired simultaneous power-up characteristic.

The same circuit also provides a power-down sequence. When the input voltage falls below U3's voltage

threshold, the ground signal is re-applied to the common track control. This pulls the track inputs to zero volts,

forcing the output of each module to follow, as shown in Figure 26. Power down is normally complete before the

input voltage has fallen below the modules' undervoltage lockout. This is an important constraint. Once the

modules recognize that an input voltage is no longer present, their outputs can no longer follow the voltage

applied at their track input. During a power-down sequence, the fall in the output voltage from the modules is

limited by the Auto-Track slew rate capability.

Notes on Use of Auto-Track™

1. The Track pin voltage must be allowed to rise above the module set-point voltage before the module

regulates at its adjusted set-point voltage.

2. The Auto-Track function tracks almost any voltage ramp during power up, and is compatible with ramp

speeds of up to 1 V/ms.

3. The absolute maximum voltage that may be applied to the Track pin is the input voltage V_I.

4. The module cannot follow a voltage at its track control input until it has completed its soft-start initialization.

This takes about 20 ms from the time that a valid voltage has been applied to its input. During this period, it

is recommended that the Track pin be held at ground potential.

5. The Auto-Track function is disabled by connecting the Track pin to the input voltage (V_I). When Auto-Track is

disabled, the output voltage rises according to its softstart rate after input power has been applied.

6. The Auto-Track pin should never be used to regulate the module's output voltage for long-term, steady-state

operation.

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R_TT

U1

Smart

Sync

AutoTrack TurboTrans

+Sense

V = 12 V

I

V

I

V

O

PTH08T240W

V

O

1 = 3.3 V

Inhibit/

UVLO Prog

−Sense

V

O

Adj

GND

+

C_O1

C_I1

R

SET1

1.62 kW

U3

8

V

CC

7

2

SENSE

5

6

RESET

RESIN

TL7712A

REF

1

3

R_TT

U2

CT

AutoTrack TurboTrans

GND

Smart

Sync

+Sense

4

R

RST

10 kW

C

T

2.2 mF

C

REF

0.1 mF

V

I

V

O

PTH08T220W

V

O

2 = 1.8 V

Inhibit/

UVLO Prog

−Sense

V

O

Adj

GND

+

C_O2

C_I2

R

SET

2

4.75 kW

Figure 24. Sequenced Power Up and Power Down Using Auto-Track

V

(1 V/div)

TRK

V

(1 V/div)

TRK

V

1 (1 V/div)

V

1 (1 V/div)

2 (1 V/div)

O

V

2 (1 V/div)

O

t − Time − 20 ms/div

t − Time − 400 ms/div

Figure 25. Simultaneous Power Up

With Auto-Track Control

Figure 26. Simultaneous Power Down

With Auto-Track Control

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PACKAGE OPTION ADDENDUM

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7-Feb-2006

PACKAGING INFORMATION

Orderable Device

PTH08T240WAD

PTH08T240WAH

PTH08T240WAS

PTH08T240WAST

PTH08T240WAZ

PTH08T240WAZT

Status ⁽¹⁾

ACTIVE

Package Package

Pins Package Eco Plan ⁽²⁾Lead/Ball Finish MSL Peak Temp ⁽³⁾

Qty

Type

Drawing

DIP MOD

ULE

EBS

11

49

Pb-Free

(RoHS)

Call TI

N / A for Pkg Type

Level-3-260C-168 HR

DIP MOD

ULE

EBS

EBT

49

TBD

DIP MOD

ULE

49

DIP MOD

ULE

250

49

DIP MOD

ULE

Pb-Free

(RoHS)

DIP MOD

ULE

250

Pb-Free

(RoHS)

⁽¹⁾The marketing status values are defined as follows:

ACTIVE: Product device recommended for new designs.

LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect.

NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in

a new design.

PREVIEW: Device has been announced but is not in production. Samples may or may not be available.

OBSOLETE: TI has discontinued the production of the device.

(2)

Eco Plan - The planned eco-friendly classification: Pb-Free (RoHS), Pb-Free (RoHS Exempt), or Green (RoHS & no Sb/Br) - please check

http://www.ti.com/productcontent for the latest availability information and additional product content details.

TBD: The Pb-Free/Green conversion plan has not been defined.

Pb-Free (RoHS): TI's terms "Lead-Free" or "Pb-Free" mean semiconductor products that are compatible with the current RoHS requirements

for all 6 substances, including the requirement that lead not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered

at high temperatures, TI Pb-Free products are suitable for use in specified lead-free processes.

Pb-Free (RoHS Exempt): This component has a RoHS exemption for either 1) lead-based flip-chip solder bumps used between the die and

package, or 2) lead-based die adhesive used between the die and leadframe. The component is otherwise considered Pb-Free (RoHS

compatible) as defined above.

Green (RoHS & no Sb/Br): TI defines "Green" to mean Pb-Free (RoHS compatible), and free of Bromine (Br) and Antimony (Sb) based flame

retardants (Br or Sb do not exceed 0.1% by weight in homogeneous material)

(3)

MSL, Peak Temp. -- The Moisture Sensitivity Level rating according to the JEDEC industry standard classifications, and peak solder

temperature.

Important Information and Disclaimer:The information provided on this page represents TI's knowledge and belief as of the date that it is

provided. TI bases its knowledge and belief on information provided by third parties, and makes no representation or warranty as to the

accuracy of such information. Efforts are underway to better integrate information from third parties. TI has taken and continues to take

reasonable steps to provide representative and accurate information but may not have conducted destructive testing or chemical analysis on

incoming materials and chemicals. TI and TI suppliers consider certain information to be proprietary, and thus CAS numbers and other limited

information may not be available for release.

In no event shall TI's liability arising out of such information exceed the total purchase price of the TI part(s) at issue in this document sold by TI

to Customer on an annual basis.

Addendum-Page 1

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型号：	PTH08T240WAS
厂家：	TEXAS INSTRUMENTS
描述：	10-A, 4.5-V to 14-V INPUT, NON-ISOLATED, WIDE-OUTPUT, ADJUSTABLE POWER MODULE WITH TURBOTRANS⑩ 10 -A ， 4.5 V至14 V输入，非隔离，宽输出，采用TurboTrans调节电源模块？电源电路输出元件输入元件
文件：	总30页 (文件大小：845K)
中文：	中文翻译
下载：	下载PDF数据表文档文件

PTH08T240WAS [TI]

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