SM73304MMX [TI]
Dual and Single Precision, 17 MHz, Low Noise, CMOS Input Amplifiers with Enable; 双核和单精度， 17兆赫，低噪声， CMOS输入放大器，使
| 型号： | SM73304MMX |
| 厂家： | 
TEXAS INSTRUMENTS |
| 描述： | Dual and Single Precision, 17 MHz, Low Noise, CMOS Input Amplifiers with Enable |
| 文件： | 总22页 (文件大小：1150K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
SM73304,SM73305
SM73304 SM73305 Dual and Single Precision, 17 MHz, Low Noise, CMOS Input
Amplifiers with Enable
Literature Number: SNOSB98
October 5, 2011
SM73304
SM73305
Dual and Single Precision, 17 MHz, Low Noise, CMOS Input
Amplifiers with Enable
General Description
Features
The SM73304/SM73305 are dual and single low noise, low
offset, CMOS input, rail-to-rail output precision amplifiers with
a high gain bandwidth product and an enable pin. The
SM73304/SM73305 are ideal for a variety of instrumentation
applications.
Unless otherwise noted, typical values at VS = 5V.
Renewable Energy Grade
Input offset voltage
Input bias current
Input voltage noise
Gain bandwidth product
Supply current (SM73305)
Supply current (SM73304)
Supply voltage range
THD+N @ f = 1 kHz
Operating temperature range
Rail-to-rail output swing
Space saving TSOT23 package (SM73305)
10-pin MSOP package (SM73304)
■
±150 μV (max)
100 fA
■
■
■
■
■
■
■
■
■
■
■
■
5.8 nV/√Hz
17 MHz
Utilizing a CMOS input stage, the SM73304/SM73305
achieve an input bias current of 100 fA, an input referred volt-
age noise of 5.8 nV/√Hz, and an input offset voltage of less
than ±150 μV. These features make the SM73304/SM73305
superior choices for precision applications.
1.15 mA
1.30 mA
1.8V to 5.5V
0.001%
−40°C to 125°C
Consuming only 1.15 mA of supply current, the SM73305 of-
fers a high gain bandwidth product of 17 MHz, enabling
accurate amplification at high closed loop gains.
The SM73304/SM73305 have a supply voltage range of 1.8V
to 5.5V, which makes these ideal choices for portable low
power applications with low supply voltage requirements. In
order to reduce the already low power consumption the
SM73304/SM73305 have an enable function. Once in shut-
down, the SM73304/SM73305 draw only 140 nA of supply
current.
Applications
Photovoltaic Electronics
■
■
■
■
Active filters and buffers
Sensor interface applications
The SM73304/SM73305 are built with National’s advanced
VIP50 process technology. The SM73305 is offered in a 6-pin
TSOT23 package and the SM73304 is offered in a 10-pin
MSOP.
Transimpedance amplifiers
Typical Performance
Offset Voltage Distribution
Input Referred Voltage Noise
30159439
30159422
© 2011 Texas Instruments Incorporated
301594
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Soldering Information
Infrared or Convection (20 sec)
Wave Soldering Lead Temp. (10 sec)
Absolute Maximum Ratings (Note 1)
If Military/Aerospace specified devices are required,
please contact the Texas Instruments Sales Office/
Distributors for availability and specifications.
235°C
260°C
Operating Ratings (Note 1)
ESD Tolerance (Note 2)
Human Body Model
Machine Model
Charge-Device Model
VIN Differential
Supply Voltage (VS = V+ – V−)
Voltage on Input/Output Pins
Storage Temperature Range
Junction Temperature (Note 3)
Temperature Range (Note 3)
−40°C to 125°C
2000V
200V
1000V
Supply Voltage (VS = V+ – V−)
0°C ≤ TA ≤ 125°C
−40°C ≤ TA ≤ 125°C
Package Thermal Resistance (θJA(Note 3))
6-Pin TSOT23
1.8V to 5.5V
2.0V to 5.5V
±0.3V
6.0V
V+ +0.3V, V− −0.3V
−65°C to 150°C
+150°C
170°C/W
236°C/W
10-Pin MSOP
2.5V Electrical Characteristics
Unless otherwise specified, all limits are guaranteed for TA = 25°C, V+ = 2.5V, V− = 0V ,VO = VCM = V+/2, VEN = V+. Boldface limits
apply at the temperature extremes.
Min
Typ
Max
Symbol
Parameter
Input Offset Voltage
Conditions
Units
μV
(Note 5) (Note 4) (Note 5)
VOS
±20
±180
±480
TC VOS Input Offset Voltage Temperature Drift SM73305
–1
±4
μV/°C
(Note 6, Note 8)
SM73304
–1.75
0.05
IB
Input Bias Current
VCM = 1.0V
1
25
−40°C ≤ TA ≤ 85°C
−40°C ≤ TA ≤ 125°C
(Note 7, Note 8)
pA
0.05
0.006
100
1
100
IOS
Input Offset Current
VCM = 1.0V
0.5
50
pA
dB
(Note 8)
CMRR Common Mode Rejection Ratio
PSRR Power Supply Rejection Ratio
83
80
0V ≤ VCM ≤ 1.4V
2.0V ≤ V+ ≤ 5.5V
85
80
100
V− = 0V, VCM = 0
dB
V
1.8V ≤ V+ ≤ 5.5V
85
98
V− = 0V, VCM = 0
CMVR Common Mode Voltage Range
−0.3
–0.3
1.5
1.5
CMRR ≥ 80 dB
CMRR ≥ 78 dB
AVOL
Open Loop Voltage Gain
SM73305, VO = 0.15 to 2.2V
RL = 2 kΩ to V+/2
88
82
98
92
SM73304, VO = 0.15 to 2.2V
RL = 2 kΩ to V+/2
84
80
dB
SM73305, VO = 0.15 to 2.2V
RL = 10 kΩ to V+/2
92
88
110
95
SM73304, VO = 0.15 to 2.2V
RL = 10 kΩ to V+/2
90
86
RL = 2 kΩ to V+/2
RL = 10 kΩ to V+/2
RL = 2 kΩ to V+/2
RL = 10 kΩ to V+/2
VOUT
Output Voltage Swing
High
25
20
30
15
70
77
60
66
mV from
either rail
Output Voltage Swing
Low
70
73
60
62
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Min
Typ
Max
Symbol
Parameter
Output Current
Conditions
Sourcing to V−
Units
(Note 5) (Note 4) (Note 5)
IOUT
36
52
30
VIN = 200 mV (Note 9)
mA
Sinking to V+
7.5
15
5.0
VIN = −200 mV (Note 9)
IS
Supply Current
SM73305
0.95
1.10
0.03
1.30
1.65
Enable Mode VEN ≥ 2.1
SM73304 (per channel)
Enable Mode VEN ≥ 2.1
Shutdown Mode (per channel)
VEN ≤ 0.4
mA
1.50
1.85
1
4
μA
SR
Slew Rate
AV = +1, Rising (10% to 90%)
8.3
10.3
14
V/μs
AV = +1, Falling (90% to 10%)
GBW
en
Gain Bandwidth
MHz
Input Referred Voltage Noise Density f = 400 Hz
f = 1 kHz
6.8
nV/
5.8
in
Input Referred Current Noise Density f = 1 kHz
0.01
pA/
ns
ton
Turn-on Time
Turn-off Time
140
1000
2 - 2.5
0 - 0.5
1.5
toff
ns
VEN
Enable Pin Voltage Range
Enable Mode
2.1
V
Shutdown Mode
VEN = 2.5V (Note 7)
VEN = 0V (Note 7)
0.4
3.0
0.1
IEN
Enable Pin Input Current
μA
0.003
0.003
THD+N Total Harmonic Distortion + Noise
f = 1 kHz, AV = 1, RL = 100 kΩ
VO = 0.9 VPP
%
0.004
f = 1 kHz, AV = 1, RL = 600Ω
VO = 0.9 VPP
5V Electrical Characteristics
Unless otherwise specified, all limits are guaranteed for TA = 25°C, V+ = 5V, V− = 0V, VCM = V+/2, VEN = V+. Boldface limits apply
at the temperature extremes.
Min
Typ
Max
Symbol
Parameter
Input Offset Voltage
Conditions
Units
μV
(Note 5) (Note 4) (Note 5)
VOS
±10
±150
±450
TC VOS Input Offset Voltage Temperataure Drift SM73305
–1
–1.75
0.1
±4
μV/°C
(Note 6, Note 8)
SM73304
IB
Input Bias Current
VCM = 2.0V
1
25
−40°C ≤ TA ≤ 85°C
−40°C ≤ TA ≤ 125°C
(Note 7, Note 8)
pA
0.1
0.01
100
100
1
100
IOS
Input Offset Current
VCM = 2.0V
0.5
50
pA
dB
(Note 8)
CMRR Common Mode Rejection Ratio
PSRR Power Supply Rejection Ratio
85
82
0V ≤ VCM ≤ 3.7V
2.0V ≤ V+ ≤ 5.5V
85
80
V− = 0V, VCM = 0
dB
1.8V ≤ V+ ≤ 5.5V
85
98
V− = 0V, VCM = 0
3
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Min
Typ
Max
Symbol
Parameter
Conditions
CMRR ≥ 80 dB
Units
(Note 5) (Note 4) (Note 5)
CMVR Common Mode Voltage Range
−0.3
–0.3
4
4
V
CMRR ≥ 78 dB
AVOL
Open Loop Voltage Gain
SM73305, VO = 0.3 to 4.7V
RL = 2 kΩ to V+/2
88
82
107
90
SM73304, VO = 0.3 to 4.7V
RL = 2 kΩ to V+/2
84
80
dB
SM73305, VO = 0.3 to 4.7V
RL = 10 kΩ to V+/2
92
88
110
95
SM73304, VO = 0.3 to 4.7V
RL = 10 kΩ to V+/2
90
86
RL = 2 kΩ to V+/2
VOUT
Output Voltage Swing
High
32
22
42
70
77
RL = 10 kΩ to V+/2
mV from
either rail
60
66
RL = 2 kΩ to V+/2
(SM73305)
Output Voltage Swing
Low
70
73
RL = 2 kΩ to V+/2
(SM73304)
50
75
78
RL = 10 kΩ to V+/2
20
66
60
62
IOUT
Output Current
Supply Current
Sourcing to V−
46
38
VIN = 200 mV (Note 9)
mA
Sinking to V+
10.5
6.5
23
VIN = −200 mV (Note 9)
IS
SM73305
1.15
1.30
0.14
1.40
1.75
Enable Mode VEN ≥ 4.6
SM73304 (per channel)
Enable Mode VEN ≥ 4.6
mA
1.70
2.05
1
4
Shutdown Mode VEN ≤ 0.4
(per channel)
μA
SR
Slew Rate
AV = +1, Rising (10% to 90%)
6.0
7.5
9.5
11.5
17
V/μs
MHz
nV/
AV = +1, Falling (90% to 10%)
GBW
en
Gain Bandwidth
Input Referred Voltage Noise Density f = 400 Hz
f = 1 kHz
7.0
5.8
in
Input Referred Current Noise Density f = 1 kHz
0.01
pA/
ns
ton
Turn-on Time
Turn-off Time
110
800
toff
ns
VEN
Enable Pin Voltage Range
Enable Mode
4.6
4.5 – 5
0 – 0.5
5.6
V
Shutdown Mode
VEN = 5V (Note 7)
VEN = 0V (Note 7)
0.4
10
IEN
Enable Pin Input Current
μA
0.005
0.001
0.2
THD+N Total Harmonic Distortion + Noise
f = 1 kHz, AV = 1, RL = 100 kΩ
VO = 4 VPP
%
0.004
f = 1 kHz, AV = 1, RL = 600Ω
VO = 4 VPP
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Note 1: Absolute Maximum Ratings indicate limits beyond which damage to the device may occur. Operating Ratings indicate conditions for which the device is
intended to be functional, but specific performance is not guaranteed. For guaranteed specifications and the test conditions, see the Electrical Characteristics
Tables.
Note 2: Human Body Model, applicable std. MIL-STD-883, Method 3015.7. Machine Model, applicable std. JESD22-A115-A (ESD MM std. of JEDEC)
Field-Induced Charge-Device Model, applicable std. JESD22-C101-C (ESD FICDM std. of JEDEC).
Note 3: The maximum power dissipation is a function of TJ(MAX), θJA. The maximum allowable power dissipation at any ambient temperature is
PD = (TJ(MAX) - TA)/θJA. All numbers apply for packages soldered directly onto a PC Board.
Note 4: Typical values represent the most likely parametric norm as determined at the time of characterization. Actual typical values may vary over time and will
also depend on the application and configuration. The typical values are not tested and are not guaranteed on shipped production material.
Note 5: Limits are 100% production tested at 25°C. Limits over the operating temperature range are guaranteed through correlations using the Statistical Quality
Control (SQC) method.
Note 6: Offset voltage average drift is determined by dividing the change in VOS at the temperature extremes by the total temperature change.
Note 7: Positive current corresponds to current flowing into the device.
Note 8: This parameter is guaranteed by design and/or characterization and is not tested in production.
Note 9: The short circuit test is a momentary open loop test.
Connection Diagrams
6-Pin TSOT23
10-Pin MSOP
30159401
Top View
30159402
Top View
Ordering Information
Package
Part Number
SM73305MK
SM73305MKE
SM73305MKX
SM73304MM
SM73304MME
SM73304MMX
Package Marking
Transport Media
NSC Drawing
1k Units Tape and Reel
250 Units Tape and Reel
3k Units Tape and Reel
1k Units Tape and Reel
250 Units Tape and Reel
3.5k Units Tape and Reel
6-Pin TSOT23
SC8B
MK06A
10-Pin MSOP
SC8B
MUB10A
5
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Typical Performance Characteristics Unless otherwise noted: TA = 25°C, VS = 5V, VCM = VS/2, VEN
=
V+.
Offset Voltage Distribution
Offset Voltage Distribution
Offset Voltage vs. VCM
TCVOS Distribution (SM73305)
TCVOS Distribution (SM73304)
Offset Voltage vs. VCM
30159481
30159403
30159422
30159480
30159410
30159411
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Offset Voltage vs. VCM
Offset Voltage vs. Supply Voltage
30159421
30159412
Offset Voltage vs. Temperature
CMRR vs. Frequency
30159456
30159409
Input Bias Current Over Temperature
Input Bias Current Over Temperature
30159423
30159424
7
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Supply Current vs. Supply Voltage (SM73305)
Supply Current vs. Supply Voltage (SM73304)
30159405
30159477
Supply Current vs. Supply Voltage (Shutdown)
Crosstalk Rejection Ratio (SM73304)
30159476
30159406
Supply Current vs. Enable Pin Voltage (SM73305)
Supply Current vs. Enable Pin Voltage (SM73305)
30159408
30159407
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Supply Current vs. Enable Pin Voltage (SM73304)
Supply Current vs. Enable Pin Voltage (SM73304)
30159478
30159479
Sourcing Current vs. Supply Voltage
Sinking Current vs. Supply Voltage
30159420
30159419
Sourcing Current vs. Output Voltage
Sinking Current vs. Output Voltage
30159450
30159454
9
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Output Swing High vs. Supply Voltage
Output Swing Low vs. Supply Voltage
30159417
30159415
Output Swing High vs. Supply Voltage
Output Swing Low vs. Supply Voltage
30159416
30159414
Output Swing High vs. Supply Voltage
Output Swing Low vs. Supply Voltage
30159418
30159413
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Open Loop Frequency Response
Open Loop Frequency Response
Phase Margin vs. Capacitive Load
Slew Rate vs. Supply Voltage
30159473
30159441
Phase Margin vs. Capacitive Load
30159445
30159446
Overshoot and Undershoot vs. Capacitive Load
30159430
30159429
11
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Small Signal Step Response
Small Signal Step Response
THD+N vs. Output Voltage
Large Signal Step Response
30159438
30159437
Large Signal Step Response
30159433
30159434
THD+N vs. Output Voltage
30159426
30159404
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THD+N vs. Frequency
THD+N vs. Frequency
30159457
30159455
PSRR vs. Frequency
Time Domain Voltage Noise
30159482
30159428
Input Referred Voltage Noise vs. Frequency
Closed Loop Frequency Response
30159439
30159436
13
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Closed Loop Output Impedance vs. Frequency
30159432
CAPACITIVE LOAD
Application Notes
The unity gain follower is the most sensitive configuration to
capacitive loading. The combination of a capacitive load
placed directly on the output of an amplifier along with the
output impedance of the amplifier creates a phase lag which
in turn reduces the phase margin of the amplifier. If phase
margin is significantly reduced, the response will be either
underdamped or the amplifier will oscillate.
SM73304/SM73305
The SM73304/SM73305 are dual and single, low noise, low
offset, rail-to-rail output precision amplifiers with a wide gain
bandwidth product of 17 MHz and low supply current. The
wide bandwidth makes the SM73304/SM73305 ideal choices
for wide-band amplification in portable applications. The low
supply current along with the enable feature that is built-in on
the SM73304/SM73305 allows for even more power efficient
designs by turning the device off when not in use.
The SM73304/SM73305 can directly drive capacitive loads of
up to 120 pF without oscillating. To drive heavier capacitive
loads, an isolation resistor, RISO in Figure 1, should be used.
This resistor and CL form a pole and hence delay the phase
lag or increase the phase margin of the overall system. The
larger the value of RISO, the more stable the output voltage
will be. However, larger values of RISO result in reduced output
swing and reduced output current drive.
The SM73304/SM73305 are superior for sensor applications.
The very low input referred voltage noise of only 5.8 nV/
at 1 kHz and very low input referred current noise of only 10
fA/
mean more signal fidelity and higher signal-to-noise
ratio.
The SM73304/SM73305 have a supply voltage range of 1.8V
to 5.5V over a wide temperature range of 0°C to 125°C. This
is optimal for low voltage commercial applications. For appli-
cations where the ambient temperature might be less than 0°
C, the SM73304/SM73305 are fully operational at supply volt-
ages of 2.0V to 5.5V over the temperature range of −40°C to
125°C.
The outputs of the SM73304/SM73305 swing within 25 mV of
either rail providing maximum dynamic range in applications
requiring low supply voltage. The input common mode range
of the SM73304/SM73305 extends to 300 mV below ground.
This feature enables users to utilize this device in single sup-
ply applications.
30159461
FIGURE 1. Isolating Capacitive Load
INPUT CAPACITANCE
The use of a very innovative feedback topology has enhanced
the current drive capability of the SM73304/SM73305, result-
ing in sourcing currents as much as 47 mA with a supply
voltage of only 1.8V.
CMOS input stages inherently have low input bias current and
higher input referred voltage noise. The SM73304/SM73305
enhance this performance by having the low input bias current
of only 50 fA, as well as, a very low input referred voltage
The SM73305 is offered in the space saving TSOT23 pack-
age and the SM73304 is offered in a 10-pin MSOP. These
small packages are ideal solutions for applications requiring
minimum PC board footprint.
noise of 5.8 nV/
. In order to achieve this a larger input
stage has been used. This larger input stage increases the
input capacitance of the SM73304/SM73305. Figure 2 shows
typical input common mode input capacitance of the
SM73304/SM73305.
National Semiconductor is heavily committed to precision
amplifiers and the market segments they serves. Technical
support and extensive characterization data is available for
sensitive applications or applications with a constrained error
budget.
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14
(2)
As shown in Equation 2, as the values of R1 and R2 are in-
creased, the magnitude of the poles are reduced, which in
turn decreases the bandwidth of the amplifier. Figure 4 shows
the frequency response with different value resistors for R1
and R2. Whenever possible, it is best to chose smaller feed-
back resistors.
30159475
FIGURE 2. Input Common Mode Capacitance
This input capacitance will interact with other impedances
such as gain and feedback resistors, which are seen on the
inputs of the amplifier to form a pole. This pole will have little
or no effect on the output of the amplifier at low frequencies
and under DC conditions, but will play a bigger role as the
frequency increases. At higher frequencies, the presence of
this pole will decrease phase margin and also causes gain
peaking. In order to compensate for the input capacitance,
care must be taken in choosing feedback resistors. In addition
to being selective in picking values for the feedback resistor,
a capacitor can be added to the feedback path to increase
stability.
30159459
FIGURE 4. Closed Loop Frequency Response
As mentioned before, adding a capacitor to the feedback path
will decrease the peaking. This is because CF will form yet
another pole in the system and will prevent pairs of poles, or
complex conjugates from forming. It is the presence of pairs
of poles that cause the peaking of gain. Figure 5 shows the
frequency response of the schematic presented in Figure 3
with different values of CF. As can be seen, using a small val-
ue capacitor significantly reduces or eliminates the peaking.
The DC gain of the circuit shown in Figure 3 is simply −R2/
R1.
30159464
FIGURE 3. Compensating for Input Capacitance
For the time being, ignore CF. The AC gain of the circuit in
Figure 3 can be calculated as follows:
30159460
FIGURE 5. Closed Loop Frequency Response
TRANSIMPEDANCE AMPLIFIER
In many applications, the signal of interest is a very small
amount of current that needs to be detected. Current that is
transmitted through a photodiode is a good example. Barcode
scanners, light meters, fiber optic receivers, and industrial
sensors are some typical applications utilizing photodiodes
(1)
This equation is rearranged to find the location of the two
poles:
15
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for current detection. This current needs to be amplified be-
fore it can be further processed. This amplification is per-
formed using a current-to-voltage converter configuration or
transimpedance amplifier. The signal of interest is fed to the
inverting input of an op amp with a feedback resistor in the
current path. The voltage at the output of this amplifier will be
equal to the negative of the input current times the value of
the feedback resistor. Figure 6 shows a transimpedance am-
plifier configuration. CD represents the photodiode parasitic
capacitance and CCM denotes the common-mode capaci-
tance of the amplifier. The presence of all of these capaci-
tances at higher frequencies might lead to less stable
topologies at higher frequencies. Care must be taken when
designing a transimpedance amplifier to prevent the circuit
from oscillating.
30159431
With a wide gain bandwidth product, low input bias current
and low input voltage and current noise, the SM73304/
SM73305 are ideal for wideband transimpedance applica-
tions.
FIGURE 7. Modified Transimpedance Amplifier
SENSOR INTERFACE
The SM73304/SM73305 have low input bias current and low
input referred noise, which make them ideal choices for sen-
sor interfaces such as thermopiles, Infra Red (IR) thermom-
etry, thermocouple amplifiers, and pH electrode buffers.
Thermopiles generate voltage in response to receiving radi-
ation. These voltages are often only a few microvolts. As a
result, the operational amplifier used for this application
needs to have low offset voltage, low input voltage noise, and
low input bias current. Figure 8 shows a thermopile applica-
tion where the sensor detects radiation from a distance and
generates a voltage that is proportional to the intensity of the
radiation. The two resistors, RA and RB, are selected to pro-
vide high gain to amplify this signal, while CF removes the high
frequency noise.
30159469
FIGURE 6. Transimpedance Amplifier
A feedback capacitance CF is usually added in parallel with
RF to maintain circuit stability and to control the frequency re-
sponse. To achieve a maximally flat, 2nd order response, RF
and CF should be chosen by using Equation 3
30159427
(3)
FIGURE 8. Thermopile Sensor Interface
Calculating CF from Equation 3 can sometimes result in ca-
pacitor values which are less than 2 pF. This is especially the
case for high speed applications. In these instances, its often
more practical to use the circuit shown in Figure 7 in order to
allow more sensible choices for CF. The new feedback ca-
pacitor, C′F, is (1+ RB/RA) CF. This relationship holds as long
as RA << RF.
PRECISION RECTIFIER
Rectifiers are electrical circuits used for converting AC signals
to DC signals. Figure 9 shows a full-wave precision rectifier.
Each operational amplifier used in this circuit has a diode on
its output. This means for the diodes to conduct, the output of
the amplifier needs to be positive with respect to ground. If
VIN is in its positive half cycle then only the output of the bot-
tom amplifier will be positive. As a result, the diode on the
output of the bottom amplifier will conduct and the signal will
show at the output of the circuit. If VIN is in its negative half
cycle then the output of the top amplifier will be positive, re-
sulting in the diode on the output of the top amplifier conduct-
ing and, delivering the signal on the amplifier's output to the
circuits output.
For R2/ R1 ≥ 2, the resistor values can be found by using the
equation shown in Figure 9. If R2/ R1 = 1, then R3 should be
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16
left open, no resistor needed, and R4 should simply be short-
ed.
30159474
FIGURE 9. Precision Rectifier
17
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Physical Dimensions inches (millimeters) unless otherwise noted
6-Pin TSOT23
NS Package Number MK06A
10-Pin MSOP
NS Package Number MUB10A
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18
Notes
19
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Notes
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Products
Applications
Communications and Telecom
Computers and Peripherals
Audio
www.ti.com/audio
amplifier.ti.com
www.ti.com/communications
www.ti.com/computers
www.ti.com/consumer-apps
www.ti.com/energy
Amplifiers
Data Converters
DLP® Products
DSP
dataconverter.ti.com Consumer Electronics
www.dlp.com
dsp.ti.com
Energy and Lighting
Industrial
www.ti.com/industrial
www.ti.com/medical
Clocks and Timers
Interface
www.ti.com/clocks
interface.ti.com
logic.ti.com
Medical
Security
www.ti.com/security
Logic
Space, Avionics and Defense
www.ti.com/space-avionics-
defense
Power Mgmt
Microcontrollers
RFID
power.ti.com
Transportation and Automotive www.ti.com/automotive
microcontroller.ti.com Video and Imaging
www.ti-rfid.com Wireless
www.ti.com/video
www.ti.com/wireless-apps
RF/IF and ZigBee® Solutions www.ti.com/lprf
TI E2E Community Home Page e2e.ti.com
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Following are URLs where you can obtain information on other Texas Instruments products and application solutions:
Products
Audio
Applications
www.ti.com/audio
amplifier.ti.com
dataconverter.ti.com
www.dlp.com
Communications and Telecom www.ti.com/communications
Amplifiers
Data Converters
DLP® Products
DSP
Computers and Peripherals
Consumer Electronics
Energy and Lighting
Industrial
www.ti.com/computers
www.ti.com/consumer-apps
www.ti.com/energy
dsp.ti.com
www.ti.com/industrial
www.ti.com/medical
www.ti.com/security
Clocks and Timers
Interface
www.ti.com/clocks
interface.ti.com
logic.ti.com
Medical
Security
Logic
Space, Avionics and Defense www.ti.com/space-avionics-defense
Transportation and Automotive www.ti.com/automotive
Power Mgmt
Microcontrollers
RFID
power.ti.com
microcontroller.ti.com
www.ti-rfid.com
Video and Imaging
www.ti.com/video
OMAP Mobile Processors www.ti.com/omap
Wireless Connectivity www.ti.com/wirelessconnectivity
TI E2E Community Home Page
e2e.ti.com
Mailing Address: Texas Instruments, Post Office Box 655303, Dallas, Texas 75265
Copyright © 2011, Texas Instruments Incorporated
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