TCM4400ETQFP [TI]
GSM/DCS BASEBAND AND VOICE A/D AND D/A RF INTERFACE CIRCUIT; GSM / DCS基带和语音A / D和D / A射频接口电路![TCM4400ETQFP](http://pdffile.icpdf.com/pdf1/p00061/img/icpdf/TCM4400_322913_icpdf.jpg)
型号: | TCM4400ETQFP |
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描述: | GSM/DCS BASEBAND AND VOICE A/D AND D/A RF INTERFACE CIRCUIT |
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TCM4400E
GSM/DCS BASEBAND AND VOICE A/D
AND D/A RF INTERFACE CIRCUIT
SLWS082A – JULY 1999 – REVISED MARCH 2000
Applications Include GSM 900,
PCS 1900, and DCS 1800 Cellular
Telephones
80-Pin TQFP (0.4 mm or 0.5 mm Lead
Pitch) or 80-Ball MicroStar BGA
Packages
MCU and DSP Serial Interface
Five Ports Auxiliary A/D
Meets JTAG Testability Standard (IEEE
Std 1131.1-1990)
Baseband Codec-GMSK Modulator
With On-Chip Burst Buffer
Voice Codec Features: Microphone
Amplifier and Bias Source,
Single 3-V Supply Voltage
Internal Voltage Reference
Extended RF Control Voltages
Advanced Power Management
GSM-Digital Audio Interface (DAI)
Programmable Gain Amplifiers, Volume
Control, and Side-Tone Control
description
The TCM4400E global system for mobile communication (GSM) baseband RF interface circuit is designed for
GSM 900 , PCS1900, and DCS 1800 European digital cellular telecommunication systems. It performs the
interface and processing of voice signals, generates baseband in-phase (I) and quadrature (Q) signals, and
controls the signals between a digital signal processor (DSP) and associated RF circuits.
The TCM4400E includes a second serial interface for use with a microcontroller. Through this interface, a
microcontroller can access all the internal registers that can be accessed through the DSP digital serial
interface. This option is intended for applications in which part of the L1 software is implemented in the
microcontroller.
A four-pin parallel port is dedicated to the full control of the digital audio interface (DAI) to the GSM system
simulator; the DAI consists of system simulator reset (SSRST) control, clock generation, and rate adaptation
with the DSP.
The voice processing portion of the device includes microphone and earphone amplifiers, analog-to-digital
(A/D) and digital-to-analog (D/A) converters, speech digital filtering, and a serial port.
The baseband processing portion of the device includes a two-channel uplink path, a two-channel downlink
path, a serial port, and a parallel port. The uplink path performs Gaussian minimum shift keying (GMSK)
modulation and D/A conversion, and it has smoothing filters to provide the external RF circuit with I and Q
baseband signals. The downlink path performs antialiasing, A/D conversion, and channel separation filtering
of the baseband I and Q signals. The serial port allows baseband data exchange with the DSP, and the parallel
port controls precise timing signals.
Auxiliary RF functions such as automatic frequency control (AFC), automatic gain control (AGC), power control,
and analog monitoring are also implemented in the TCM4400E. Internal functional blocks of the device can be
separately and automatically powered down with GSM RF windows.
These devices have limited built-in ESD protection. The leads should be shorted together or the device placed in conductive foam
during storage or handling to prevent electrostatic damage to the MOS gates.
Please be aware that an important notice concerning availability, standard warranty, and use in critical applications of
Texas Instruments semiconductor products and disclaimers thereto appears at the end of this data sheet.
MicroStar BGA is a trademark of Texas Instruments.
Copyright 2000, Texas Instruments Incorporated
PRODUCTION DATA information is current as of publication date.
Products conform to specifications per the terms of Texas Instruments
standard warranty. Production processing does not necessarily include
testing of all parameters.
1
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TCM4400E
GSM/DCS BASEBAND AND VOICE A/D
AND D/A RF INTERFACE CIRCUIT
SLWS082A – JULY 1999 – REVISED MARCH 2000
80-Pin TQFP PACKAGE
(TOP VIEW)
80 79 78 77 76 75 74 73 72 71 70 69 68 67 66 65 64 63 62 61
BFSX
BCLKX
BDX
BDR
BCLKR
BFSR
BULIP
BULIN
BULQP
BULQN
1
60
59
58
57
56
55
54
53
52
51
50
49
48
47
46
45
44
43
42
41
2
3
4
AV
5
DD2
AV
6
SS2
AV
BDLIN
BDLIP
BDLQN
BDLQP
VMID
7
DD1
V
8
REF
IBIAS
VGAP
9
10
11
12
13
14
15
16
17
18
19
20
AV
SS1
RESET
DV
SS3
VFS
VDX
VDR
AV
SS3
APC
AFC
AGC
ADCMID
VCLK
SSRST
SSDX
SSDR
SSCLK
AV
DD5
DV
DD3
AV
DD3
21 22 23 24 25 26 27 28 29 30 31 32 33 34 35 36 37 38 39 40
2
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TCM4400E
GSM/DCS BASEBAND AND VOICE A/D
AND D/A RF INTERFACE CIRCUIT
SLWS082A – JULY 1999 – REVISED MARCH 2000
GGM PACKAGE
(TOP VIEW)
K
J
K2
J2
K3
J3
K4
J4
H4
K5
J5
H5
K6
J6
H6
K7
J7
H7
K8
J8
K9
J9
NC
J1
NC
J10
H10
G10
F10
E10
D10
C10
B10
AV
DD3
SSCLK
DV
DD3
AV
SS4
TRST
SSDX
ADCMID
AGC
H
H1
G1
F1
E1
D1
C1
B1
H2
G2
F2
H3
G3
F3
H8
G8
F8
E8
D8
C8
B8
A8
H9
G9
F9
E9
D9
C9
B9
SSDR
MICIN
AV
DD5
AFC
APC
VDR
G
F
AV
VCLK
SSRST
RESET
SS3
VMID
DV
SS3
VFS
VDX
IBIAS
BDLQP
BDLIN
BDLQN
E
E2
D2
E3
D3
AV
SS1
BFSR
BDLIP
AV
AV
DD2
SS2
AV
D
C
B
A
DD1
V
REF
BDR
TCK
BULQP
BCLKR
C2
B2
C3
B3
A3
C4
B4
A4
C5
B5
A5
C6
B6
C7
B7
A7
BDX
BFSX
TDI
BULIP
BCLKX
MCLK
TDO
NC
1
A2
2
A6
6
A9
9
NC
10
3
4
5
7
8
NC – No internal connection
3
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TCM4400E
GSM/DCS BASEBAND AND VOICE A/D
AND D/A RF INTERFACE CIRCUIT
SLWS082A – JULY 1999 – REVISED MARCH 2000
functional block diagram
45
47
Auxiliary DAC
Analog AGC
AGC
APC
GSM Windows
Timing
Interface
Main Clock
Generator
JTAG
Interface
Power
Management
APC (D/A)
RF TX Ramp
60
75
78
76
77
BULIP
USEL
UCLK
UDX
Baseband Uplink GMSK Modulator
Internal Burst RAM
Automatic Offset Compensation
8-Bit DAC and Smoothing Filter
MCU
Serial
Interface
59
57
BULIN
BULQN
58
UDR
BULQP
Bus
Controller
1
3
2
6
4
BFSX
BDX
53
54
52
51
BDLIP
BDLIN
BDLQN
BDLQP
DSP
Serial
Interface
Baseband Downlink I/Q Path
Automatic Offset Compensation
10-Bit ADC and Antialiasing Filter
BCLKX
BFSR
BDR
5
BCLKR
AGC, AFC
APC Output
Swing Control
43
46
AV
DD5
16
13
14
15
VCLK
VFS
Voiceband
Serial
Interface
Voice Uplink 13 Bit ADC
Two Analog Inputs
Programmable Gain
Bandpass Digital Filter
VDX
VDR
AFC (D/A)
VTCXO Control
AFC
Side-tone
36
37
38
39
40
ADIN1
ADIN2
ADIN3
ADIN4
ADIN5
Voice Downlink 13 Bit DAC
Auxiliary Earphone Output
Programmable Volume
Smoothing Filter
20
17
18
19
SSCLK
SSRST
SSDX
Auxiliary
10 Bits
5 Inputs ADC
I
-V
VMID
Bias
REF REF
DAI
Interface
Bandpass Digital Filter
SSDR
4
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TCM4400E
GSM/DCS BASEBAND AND VOICE A/D
AND D/A RF INTERFACE CIRCUIT
SLWS082A – JULY 1999 – REVISED MARCH 2000
Terminal Functions
TERMINAL
NO.
QFP BGA
I/O
DESCRIPTION
NAME
ADCMID
ADIN1
ADIN2
ADIN3
ADIN4
ADIN5
AFC
44
36
37
38
39
40
46
45
47
29
34
7
H8
J7
I/O Reference voltage of auxiliary A/D converters; decoupling only (analog)
I
I
Auxiliary 10-bit ADC input 1 (analog)
H7
K8
J8
Auxiliary 10-bit ADC input 2 (analog)
I
Auxiliary 10-bit ADC input 5 (analog)
I
Auxiliary 10-bit ADC input 4 (analog)
K9
G9
H10
G10
K5
H6
D1
D9
J9
I
Auxiliary 10-bit ADC input 3 (analog)
O
O
O
I
Automatic frequency control DAC output (analog)
Automatic gain control DAC output (analog)
AGC
APC
Automatic power control DAC output (analog)
AUXI
Auxiliary (high-level) speech signal input (analog)
Auxiliary downlink (voice codec) amplifier output, single-ended (analog)
Analog positive power supply (bandgap, internal common-mode generator, bias current generator).
Analog positive power supply (baseband CODEC)
Analog positive power supply (auxiliary RF functions)
Analog positive power supply (voice codec)
AUXO
O
AV
AV
AV
AV
AV
AV
AV
AV
AV
DD1
DD2
DD3
DD4
DD5
SS1
SS2
SS3
SS4
56
41
30
43
11
55
48
31
72
5
J5
H9
E3
D10
G8
H5
A5
C1
B1
C3
C2
C6
C5
D2
B2
E8
E9
E10
F8
Analog positive power supply (output stages of auxiliary RF functions).
Analog negative power supply (bandgap, internal common-mode generator, bias current generator).
Analog negative power supply (baseband CODEC)
Analog negative power supply (auxiliary RF functions)
Analog negative power supply (voice codec)
BCAL
I
Baseband uplink or downlink offset calibration enable (timing interface)
BCLKR
BCLKX
BDR
I/O DSP serial interface clock input. This clock signal is provided by the DSP or the TCM4400E (digital/3-state).
2
O
I
DSP serial interface clock output. The frequency is the same as MCLK (digital/3-state).
DSP serial interface serial data input (digital)
4
BDX
3
O
I
DSP serial interface serial data output (digital/3-state)
BENA
BDLON
BFSR
71
74
6
Burst transmit or receive enable (depends on status of BULON and BDLON) (digital)
Power on of baseband downlink (timing interface)
I
I
DSP serial interface receive frame synchronization input (digital)
DSP serial interface transmit frame synchronization output (digital/3-state)
In-phase baseband input (–) downlink path (analog)
BFSX
1
O
I
BDLIN
BDLIP
BDLQN
BDLQP
BULIN
BULIP
BULON
BULQN
BULQP
54
53
52
51
59
60
73
57
58
80
66
42
I
In-phase baseband input (+) downlink path (analog)
I
Quadrature baseband input (–) downlink path (analog)
Quadrature baseband input (+) downlink path (analog)
In-phase baseband output (–) uplink path (analog)
I
C9
B10
B5
D8
C10
A2
B7
J10
O
O
I
In-phase baseband output (+) uplink path (analog)
Serial clock input (serial interface) (digital)
O
O
Negative quadrature baseband output. BULQN is an uplink path (analog)
Positive quadrature baseband output. BULQN is an uplink path (analog)
Digital positive power supply (baseband and timing serial interfaces)
Digital positive power supply (baseband CODEC)
DV
DV
DV
DD1
DD2
DD3
Digital positive power supply (auxiliary RF functions)
5
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TCM4400E
GSM/DCS BASEBAND AND VOICE A/D
AND D/A RF INTERFACE CIRCUIT
SLWS082A – JULY 1999 – REVISED MARCH 2000
Terminal Functions (Continued)
TERMINAL
NO.
QFP BGA
I/O
DESCRIPTION
NAME
DV
21
79
J2
Digital positive power supply (voiceband codec and serial interface)
Digital negative power supply (baseband and timing serial interfaces)
DD4
SS1
DV
B3
DV
DV
DV
65
49
22
33
32
25
35
9
A8
F10
K2
J6
Digital negative power supply (baseband CODEC)
Digital negative power supply (auxiliary RF functions)
Digital negative power supply (voiceband codec and serial interface)
Earphone amplifier output (–) (analog)
SS2
SS3
SS4
EARN
O
O
EARP
K6
K3
K7
E1
B6
J4
Earphone amplifier output (+) (analog)
GNDA1
GNDA2
IBIAS
Analog signal ground for the microphone amplifier and auxiliary input
Signal return (ground) for AUXO output
I/O Internal bias reference current adjust. IBIAS adjusts the reference current with an external resistor (analog).
MCLK
70
26
I
I
Master system clock input (13 MHz)
MICBIAS
Microphone bias supply output. MICBIAS is also used to decouple bias supply with an external capacitor
(analog).
MICIP
MICIN
PWRDN
RESET
SSCLK
SSDR
SSDX
SSRST
TCK
27
28
23
12
20
19
18
17
64
63
62
69
68
67
61
24
78
77
76
75
16
15
14
13
10
50
K4
H4
J3
I
I
Positive microphone amplifier input (analog)
Negative microphone amplifier input (analog)
Power-down mode control input (digital), active high
Device global hardware reset (digital), active low
DAI external 104 kHz clock output (digital)
I
F1
J1
I
O
I
H2
H1
G3
C8
B8
A9
A6
C7
A7
B9
H3
A3
C4
B4
A4
G2
G1
F3
F2
E2
F9
DAI data transfer input. SSDR connects to GSM-SS TDAI (digital/pullup).
DAI data transfer output SSDX connects to GSM-SS RDAI (digital).
DAI reset input (digital/pullup)
O
I
I
Scan test clock (digital/pulldown)
TDI
I
Scan path input (for testing purposes) (digital/pullup)
Scan path output (for testing purposes) (digital/3-state)
TDO
I
TEST1
TEST2
TEST3
TMS
I/O Test I/O (digital/3-state & pullup)
I/O Test I/O (digital/3-state & pullup)
O
I
Test output (digital)
JTAG test mode select (digital/pullup)
TRST
UCLK
UDR
I
JTAG serial interface & boundary scan register reset (digital/pullup), active low.
MCU interface clock input (digital)
I
I
MCU interface data transfer input (digital)
UDX
O
I
MCU interface data transfer output (digital/3-state)
MCU serial interface select (digital)
USEL
VCLK
VDR
O
I
Voiceband serial interface clock output (digital/3-state)
Voiceband serial interface receive data input (digital)
Voiceband serial interface transmit data output (digital/3-state)
Voiceband serial interface transmit frame synchronization output (digital/3-state)
VDX
O
O
VFS
VGAP
VMID
I/O Bandgap reference voltage. VGAP decouples with an external capacitor (analog)
O
Baseband uplink midrail voltage output. VMID serves as a reference common-mode voltage for a RF device
when directly dc coupled (analog)
V
REF
8
D3
I/O Reference voltage V decouples with an external capacitor (analog).
REF
6
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TCM4400E
GSM/DCS BASEBAND AND VOICE A/D
AND D/A RF INTERFACE CIRCUIT
SLWS082A – JULY 1999 – REVISED MARCH 2000
†
absolute maximum ratings over operating free-air temperature range (unless otherwise noted)
Supply voltage range, AV , DV
Maximum voltage on any input, V max . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . V
(see Note 1) . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . –0.3 to 6 V
DD
DD
I
+0.3 V / V –0.3 V
SS
DD
Storage temperature, T
. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . –65°C to 150°C
stg
Maximum junction temperature, T . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 150°C
J
†
Stresses beyond those listed under “absolute maximum ratings” may cause permanent damage to the device. These are stress ratings only, and
functional operation of the device at these or any other conditions beyond those indicated under “recommended operating conditions” is not
implied. Exposure to absolute-maximum-rated conditions for extended periods may affect device reliability.
NOTE 1: Voltage measurements with respect to GND.
recommended operating conditions
MIN NOM
MAX
3.3
UNIT
Vdc
°C
Supply voltage range (AV , DV
DD
)
2.7
–25
3.0
DD
Operating temperature range
85
Digital I/O voltage with respect to DV
SS
–0.3
–0.3
DV
AV
+ 0.3
Vdc
V
DD
Analog I/O voltage with respect to AV
+ 0.3
SS
DD
DD
Difference between any AV
DD
or DV
0.3
V
electrical characteristics over recommended operating free-air temperature range (unless
otherwise noted)
digital inputs and outputs
PARAMETER
Low-level output current with digital pad lower than 0.1 V (CMOS)
Low-level output current with digital pad lower than 0.4 V (TTL)
MIN
0
TYP
MAX
40
1
UNIT
µA
mA
µA
mA
V
0
High-level output current with digital pad higher than V –0.1 V (CMOS)
DD
–40
–1
0
High-level output current with digital pad higher than V –0.4 V (TTL)
DD
0
Minimum high-level input voltage, V
V
–0.3
dd
IH
IL
Maximum low level input voltage, V
Vss+0.3
15
V
Output current on high impedance state outputs
Input current (any input) when input high
–15
–1
µA
µA
µA
µA
Input current (standard inputs) when input low
1
Input current (inputs with pullup TMS, TDI ,TEST1 ,TEST2) when input low
15
7
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TCM4400E
GSM/DCS BASEBAND AND VOICE A/D
AND D/A RF INTERFACE CIRCUIT
SLWS082A – JULY 1999 – REVISED MARCH 2000
electrical characteristics over recommended operating free-air temperature range (unless
otherwise noted) (continued)
voltage references
REFERENCE
Voltage on band gap (used for all other references)
Band gap output resistance
MIN
TYP
1.22
200
0.1
MAX
UNIT
Vdc
KΩ
µF
VGAP
VREF
VMID
1.16
1.28
Band gap external decoupling capacitance
Band gap start time ( bit CHGUP=0 )
100
2.5
ms
Band gap start time ( bit CHGUP=1)
ms
Voltage reference of GMSK internal ADC and DAC : V
Voltage reference output resistance
1.66
1.75
200
0.1
1.84
Vdc
KΩ
µF
VREF
Voltage reference external decoupling capacitance
Voltage reference start time ( bit CHGUP=0 )
Voltage reference start time ( bit CHGUP=1)
300
10
ms
ms
Common-mode reference for baseband uplink: V
Common-mode reference for baseband uplink: V
Load resistance on Vmid output
(Bit SELVMID=0)
(Bit SELVMID=1)
–10% Vdd/2
10%
1.45
Vdc
Vdc
KΩ
Vdc
Vdc
µA
VMID
1.25
10
1.35
VMID
MICBIAS Microphone-driving voltage (Bit MICBIAS=0)
Microphone-driving voltage(Bit MICBIAS=1)
1.80
2.25
450
350
2.00
2.5
2.20
2.75
Microphone-bias current drive capability (Bit MICBIAS= 1)
Microphone-bias current drive capability (Bit MICBIAS=0 )
ADCMID DC bias reference of the auxiliary ADCs
ADCMID external decoupling capacitance
500
400
µA
–10% Vdd/2
10%
Vdc
µF
0.1
IBIAS
Bias current adjust external resistance
100
KΩ
master clock input (MCLK)
PARAMETER
MIN
NOM
MAX
UNIT
Master clock signal frequency
Master clock duty cycle (Sinewave)
Maximum peak-to-peak amplitude
Minimum peak-to-peak amplitude
Common-mode input voltage
13
MHz
40%
60%
1.3
Vpp
Vpp
Vdc
0.5
+0.5
V
V
–0.5
SS
DD
Input resistance at 13MHz (MCLK to ground)
Input capacitance at 13 MHz (MCLK to ground)
4.1
5
6.5
18
KΩ
12.5
15
pf
baseband uplink path
PARAMETER
TEST CONDITIONS
MIN
TYP
MAX
UNIT
bit
I and Q D/A converters resolution
Dynamic range on each output
8
Centered on V
V
VREF
Vpp
Vpp
Vpp
kΩ
VMID
†
†
Differential output dynamic range with OUTLEV bit = 0
Differential output dynamic range with OUTLEV bit = 1
Output load resistance, differential
Output load capacitance, differential
Output common-mode voltage
BULQP-BULQN or BULIP-BULIN
2 x V
VREF
BULQP-BULQN or BULIP-BULIN
8/15 x V
VREF
10
50
pF
Programmable by bit SELVMID
V
V
VMID
Hi-Z
and BULQP–BULQN=0 corresponding to a phase angle of 0°.
I & Q output state in power down
†
Initial value after reset and at beginning of each burst are BULIP–BULIN=V
REF
8
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TCM4400E
GSM/DCS BASEBAND AND VOICE A/D
AND D/A RF INTERFACE CIRCUIT
SLWS082A – JULY 1999 – REVISED MARCH 2000
electrical characteristics over recommended operating free-air temperature range (unless
otherwise noted) (continued)
dc accuracy – baseband uplink path
PARAMETER
MIN
TYP
±100
0
MAX
UNIT
mV
Offset error before calibration
†
Offset error after calibration
–7
7
mV
†
Calibration must be performed in normal operation mode.
dynamic parameters – baseband uplink path
PARAMETER
TEST CONDITIONS
MIN
TYP
MAX
1.5
UNIT
dB
Absolute gain error relative to V
Measured with 67.7 kHz sinewave
–1.5
0
VREF
100 kHz
200 kHz
250 kHz
400 kHz
600 KHz
–3
dB
–34
–37
–65
–72
dB
Maximumoutputrandommodulationspectrumrelativetoin-band
averagelevel. MeasuredbyaverageFFTsofrandomburstsusing
a window with 30 kHz bandwidth.
dB
dB
dB
800 KHz
–72
dB
smoothing filters characteristics – baseband uplink path
PARAMETER
TEST CONDITIONS
MIN
TYP
MAX
UNIT
Group delay
0 Hz to 100 kHz
1.5
µs
I and Q channels gain matching – baseband uplink path
PARAMETER
TEST CONDITIONS
MIN
TYP
MAX
UNIT
Gain matching between channels
0 Hz to 96 kHz
Measured on 67.7 kHZ sinewave
–1
0
1
dB
–0.42 –0.27 –0.12
I and Q gain unbalance
Programmable with bits IQSEL, G1, and G0
dB
–0.68 –0.53 –0.38
–0.93 –0.78 –0.63
baseband uplink path global characteristics
PARAMETER
MIN
TYP
MAX
6°
UNIT
peak
rms
‡
GMSK phase trajectory error
1.5°
Power supply rejection
55
dB
‡
After software calibration through BBAloop
timing requirements of baseband uplink path
programmable delays – baseband uplink path (see Figure 1)
§
MIN NOM
MAX
UNIT
t
t
Setup time, BENA before APC↑
Bits DELU of register BULRUDEL
Bits DELD of register BULRUDEL
Bit APCSPD = 0
0
0
15 1/4-bit
15 1/4-bit
su1
Hold time, ramp-down from BENA low
h1
1/16-bit
64
t , t
r f
Transition time, APC
0
Bit APCSPD = 1
1/8-bit
§
Bit is relative to GSM bit = 1/270 kHz. Units can be a fractional part of the GSM bit as noted. Values in the above table are given for system
information only.
9
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TCM4400E
GSM/DCS BASEBAND AND VOICE A/D
AND D/A RF INTERFACE CIRCUIT
SLWS082A – JULY 1999 – REVISED MARCH 2000
timing requirements of baseband uplink path (continued)
fixed delays – baseband uplink path (see Figure 1)
†
MIN NOM
MAX UNIT
t
t
t
t
t
t
t
Setup time, BULON↑ to BCAL↑
Pulse duration, BCAL high
15
132
0
µs
µs
µs
su2
w1
Setup time, BCAL low before BENA↑
Pulse duration, BENA high
su3
w2
N effective duration of burst controlled by BENA
(Digital delay of modulator)
N–32
32
1/4-bit
1/4 bit
bit
Hold time, modulation low after BENA low
Hold time, BULON↓ after APC low
Input-to-output modulator delay
h2
1
h3
1.5
bit
dd(mod)
†
Bit is relative to GSM bit = 1/270 kHz. Units can be a fractional part of the GSM bit as noted. Values in the above table are given for system
information only.
baseband downlink path
PARAMETER
TEST CONDITIONS
MIN
TYP
MAX
UNIT
Vpp
Vpp
kΩ
Centered on external common
Dynamic range on each input
V
VREF
mode (V
)
BDLCOM
Differential input dynamic range
DLQP–DLQN or DLIP–DLIN
2*V
VREF
Differential input resistance at BDLQP–BDLQN or
BDLIP–BDLIN
130
1.5
90
200
270
6.5
180
12
Differential input capacitance at BDLQP–BDLQN or
BDLIP–BDLIN
4
pF
Single ended input resistance at BDLQPor BDLQN or BDLIP
or BDLIN to ground.
130
8
kΩ
Single ended input capacitance at BDLQP or BDLQN or
BDLIP or BDLIN to ground.
6
pF
V
External common-mode input voltage: V
0.8
V
DD
/2
V
–0.8
BDLCOM
DD
Maximum digital code value on
16-bit I and Q samples.
Range of digital output data
±21060
dc accuracy – baseband downlink path
PARAMETER
TEST CONDITIONS
MIN
TYP
0
MAX
UNIT
LSB
LSB
‡
Offset error before calibration
Offset error after calibration,
Offset correction range
–60
–2
60
2
‡
± 21 on 16-bit I and Q words
0
Full scale
‡
The LSB corresponds to the one of the ADC which is specified with 66 dB dynamic range (±1024),which means 11-bit, but the output data bits
are transmitted through the serial interface with 16-bit words. On top of that, the decimation ratio of 24 (6.5 MHz/270 kHz) makes the maximum
code on a 16-bit word to be 21060 instead of 32767. So one LSB of the ADC corresponds to a value of 21060/1024 = 20.57 on the 16-bit output
serial words on I and Q.
channel characteristics
frequency response – baseband downlink path
PARAMETER
MIN
–0.3
–0.3
–4
TYP
MAX
0.25
0.25
0.3
UNIT
< 67.5 Hz
67.5 kHz
96 kHz
Frequency response of the total path with values referenced to 18 kHz
dB
135 kHz
200 kHz
400 kHz
–40
–40
–40
10
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TCM4400E
GSM/DCS BASEBAND AND VOICE A/D
AND D/A RF INTERFACE CIRCUIT
SLWS082A – JULY 1999 – REVISED MARCH 2000
channel characteristics (continued)
SNR vs signal level–baseband downlink path
PARAMETER
TEST CONDITIONS
MIN
21
26
36
46
50
55
30
TYP
MAX
UNIT
dB
–50 dBm0 200 kHz bandwidth
–40 dBm0
–30 dBm0
Signal level
–20 dBm0
–10 dBm0
–5 dBm0
0 dBm0
Idle channel noise, 0 Hz –200 kHz
–66
dBm0
gain characteristics of the baseband downlink path
PARAMETER
TEST CONDITIONS
at –10 dBm0 and 18 kHz
0 dBm0
MIN
–11
TYP
MAX
–9
UNIT
Absolute gain error relative to V
–10
dB
VREF
–0.25
–0.25
0.25
0.25
–5 dBm0
–10 dBm0 Reference level
–20 dBm0
0
dB
dB
Gain tracking error. Over the range 3 dBm0 to – 50 dBm0 at
18 kHz with reference –10 dBm0
–0.25
–0.25
–0.25
–0.50
0.25
0.25
0.25
0.50
–30 dBm0
–40 dBm0
–50 dBm0
group delay – baseband downlink path
PARAMETER
MIN
TYP
MAX
UNIT
Group delay
0 Hz to 100 kHz
28
µs
I and Q channels matching – baseband downlink path
PARAMETER
TEST CONDITIONS
18 kHz sinewave
MIN
–0.5
–8
TYP
MAX
0.5
8
UNIT
dB
Gain matching between channels
Delay matching between channels
0 Hz to 96 kHz
0 Hz to 96 kHz
18 kHz sinewave
ns
baseband downlink path global characteristics
PARAMETER
TEST CONDITIONS
MIN
TYP
MAX
UNIT
Power supply rejection, 0 Hz –100 kHz band
70
dB
timing requirements of baseband downlink path (see Figure 2)
†
MIN NOM
MAX UNIT
t
t
t
t
t
t
t
Setup time, BDLON↑ to BCAL↑
Pulse duration, BCAL
5
60
µs
µs
µs
su4
w3
su5
w4
su6
h4
Setup time BCAL low before BENA↑
Pulse duration, BENA high
0
N effective duration of burst controlled by BENA
N
1/4-bit
µs
Setup time, BENA↑ before DATAOUT VALID
Hold time, DATAOUT VALID after BENA↓
Hold time, BDLON low after BENA low
24.3
28
3.7
µs
0
µs
h5
†
Values in the above table are given for system information only.
11
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TCM4400E
GSM/DCS BASEBAND AND VOICE A/D
AND D/A RF INTERFACE CIRCUIT
SLWS082A – JULY 1999 – REVISED MARCH 2000
automatic power control (APC)
APC level (8-bit DAC)
PARAMETER
TEST CONDITIONS
MIN
–1
TYP
TYP
MAX
1
UNIT
LSB
µs
Integral nonlinearity (best fitting)
Shaper at maximum full scale Load 10 kΩ, 50 pF
Differential nonlinearity
Settling time
–1
1
10
APC shaper (5-bit DAC)
PARAMETER
TEST CONDITIONS
MIN
–1
MAX
UNIT
LSB
LSB
µs
Integral nonlinearity (best fitting )
Differential nonlinearity
1
1
1
–1
†
Settling time
†
Value given for system information only.
APC output stage
PARAMETER
TEST CONDITIONS
MIN
2.0
0
TYP
MAX
2.4
20
UNIT
V
Output voltage at shape=31 & level =255
Output voltage at shape=0 & level=xx
Output voltage at shape=0 & level =xx
Output voltage at shape=xx & level = 0
Output voltage in power-down
DC power supply sensitivity
2.2
Bit APCMODE = 0
Bit APCMODE =1
mV
mV
mV
V
80
120
0
160
5
0
1%
50
Output impedance in power-down
Load resistance
20
Ω
10
kΩ
pF
Load capacitance
monitoring ADC
10-bit ADC
PARAMETER
TEST CONDITIONS
MIN
TYP
MAX
UNIT
LSB
LSB
µs
Integral nonlinearity (Best fitting)
Differential nonlinearity
Input signal range < 0.95 V
Input signal range < 0.95 V
–4
–2
4
2
VREF
VREF
†
Conversion time
Input range
10
0
V
VREF
10
V
Input leakage current
Input capacitance
–10
µA
25
pF
†
Value given for system information only.
12
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TCM4400E
GSM/DCS BASEBAND AND VOICE A/D
AND D/A RF INTERFACE CIRCUIT
SLWS082A – JULY 1999 – REVISED MARCH 2000
automatic Gain Control (AGC)
AGC 10-bit DAC
PARAMETER
TEST CONDITIONS
Best fitting line
MIN
–1
TYP
MAX
1
UNIT
LSB
LSB
µs
Integral nonlinearity
Differential nonlinearity
Settling time
–1
1
From AUXAGC load
100
AGC output stage
PARAMETER
TEST CONDITIONS
MIN
1.9
TYP
2.2
0.24
0
MAX
2.4
UNIT
Output voltage with code max
Offset voltage with code 000
Output voltage in power down
DC power supply sensitivity
Output impedance in power down
Load resistance
V
V
V
0.18
0.30
1%
50
200
kΩ
kΩ
pF
10
Load capacitance
automatic frequency control (AFC)
AFC 13-bit DAC
PARAMETER
TEST CONDITIONS
MIN
TYP
2
MAX
UNIT
AFCCK1=1
AFCCK0 = 1
AFCCK0 = 0
AFCCK0 = 1
AFCCK0 = 0
AFCCK1=1
AFCCK1=0
AFCCK1=0
Best fitting line
1
Sampling frequency, f
MHz
s
0.5
0.25
±1
Integral nonlinearity from 0 to 75% output range
Differential nonlinearity from 0 to 75% output range
Settling time
LSB
LSB
µs
±1
1
DC power-supply sensitivity
Over power supply range
1%
AFC output stage
PARAMETER
TEST CONDITIONS
MIN
TYP
25
33
2.5
3
MAX
UNIT
kΩ
nF
V
Internal output resistance (±30 % tolerance)
External filtering capacitance
Output voltage with code max
Output voltage with code min
Output voltage in power down
2.0
0
2.8
6
mV
V
0
Output impedance in power down
25
kΩ
13
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TCM4400E
GSM/DCS BASEBAND AND VOICE A/D
AND D/A RF INTERFACE CIRCUIT
SLWS082A – JULY 1999 – REVISED MARCH 2000
voice uplink path
global characteristics of voice uplink path
PARAMETER
TEST CONDITIONS
MIN
TYP
MAX
UNIT
Inputs 3 dBm0 (maximum digital sample amplitude)
with PGA gain, set to 0dB (default value)
Maximum input range (MICP – MICN)
32.5
mVrms
Nominal reference level (MICP – MICN)
Differential input resistance (MICP – MICN)
Micro-amplifier gain
–10
140
27
dBm0
kΩ
90
200
dB
Inputs 3 dBm0 (maximum digital sample amplitude)
with PGA gain, set to 0dB (default value)
Maximum input range at AUXI
365
mVrms
Nominal reference level at AUXI
Input resistance at AUXI
Auxi amplifier gain
–10
220
6
dBm0
kΩ
140
300
dB
PGA absolute gain
4.6
dB
VULPGA code =10000
VULPGA code = 10111
VULPGA code = 11000
VULPGA code = 11001
VULPGA code = 11010
VULPGA code = 11011
VULPGA code = 00000 (default)
VULPGA code = 00001
VULPGA code = 00010
VULPGA code = 00011
VULPGA code = 00100
VULPGA code = 00101
VULPGA code = 00110 (ref)
VULPGA code = 00111
VULPGA code = 01000
VULPGA code = 01001
VULPGA code = 01010
VULPGA code = 01011
VULPGA code = 01100
VULPGA code = 10001
VULPGA code = 10010
VULPGA code = 10011
VULPGA code = 10100
VULPGA code = 10101
VULPGA code = 10110
–12 dB
–11 dB
–10 dB
–9 dB
–8 dB
–7 dB
–6 dB
–5 dB
–4 dB
–3 dB
–2 dB
–1 dB
0 dB
–12.7 –12.2 –11.7
–11.3 –10.8 –10.3
–10.6 –10.1
–9.6
–8.5
–7.5
–6.5
–5.7
–4.6
–3.6
–2.5
–1.4
–0.5
–9.5
–8.5
–7.5
–6.7
–5.6
–4.6
–3.5
–2.4
–1.5
–9
–8
–7
–6.2
–5.1
–4.1
–3
–1.9
–1
PGA gain step
0
dB
1 dB
0.7
1.4
2.6
3.6
4.5
5.3
6.4
7.4
8.6
9.6
10.5
11.5
1.2
1.9
3.1
4.1
5
1.7
2.4
2 dB
3 dB
3.6
4 dB
4.6
5 dB
5.5
6 dB
5.8
6.9
7.9
9.1
10.1
11
6.3
7 dB
7.4
8 dB
8.4
9 dB
9.6
10 dB
11 dB
12 dB
10.6
11.5
12.5
12
Power supply rejection, 0 Hz –100 kHz band
70
dB
14
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TCM4400E
GSM/DCS BASEBAND AND VOICE A/D
AND D/A RF INTERFACE CIRCUIT
SLWS082A – JULY 1999 – REVISED MARCH 2000
voice uplink path (continued)
frequency response of the voiceband uplink path
PARAMETER
MIN
TYP
–37.4
–25.9
–16.5
MAX
–20
–15
–10
1
UNIT
TEST CONDITIONS
100 Hz
150 Hz
200 Hz
300 Hz
–2 –1.46
0
1000 Hz
2000 Hz
3000 Hz
3400 Hz
3600 Hz
3800 Hz
4000 Hz
>4600 Hz
Reference point is 1000 Hz
–1.5 –0.58
–1.5 –0.77
1
1
Frequency response (Gain relative to reference gain at
1 kHz)
dB
–2
–1
–12.4
–23.3
–35
1
–6
–18
–30
–40
>–52
psophometric SNR vs signal level of the voiceband uplink path
PARAMETER
TEST CONDITIONS
MIN
35
40
42
45
42
40
30
25
TYP
MAX
UNIT
3 dBm0
0 dBm0
–5 dBm0
–10 dBm0
–20 dBm0
–30 dBm0
–40 dBm0
–45 dBm0
0 Hz –4 kHz
Signal to noise + distortion
dB
Maximum idle channel noise
–72 dBm0
Crosstalk with the downlink path
Downlink path loaded with 150 Ω
–66
dB
gain characteristics of the voiceband uplink path
PARAMETER
TEST CONDITIONS
at 0dBm0 and 1KHz
MIN
–1
TYP
MAX
1
UNIT
Absolute gain error
dB
at –10dBm0 and 1KHz
–11
–10
–9
3 dBm0
–0.25
–0.25
–0.25
0.25
0.25
0.25
0 dBm0
–5 dBm0
–10 dBm0 Reference level
–20 dBm0
0
Gain tracking error. Over the range 3 dBm0 to – 45 dBm0 at
1 kHz with reference –10 dBm0
dB
–0.25
–0.25
–0.35
–0.50
0.25
0.25
0.35
0.50
–30 dBm0
–40 dBm0
–45 dBm0
15
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TCM4400E
GSM/DCS BASEBAND AND VOICE A/D
AND D/A RF INTERFACE CIRCUIT
SLWS082A – JULY 1999 – REVISED MARCH 2000
voice downlink path
global characteristics of voice downlink path
PARAMETER
TEST CONDITIONS
MIN
3.1
1.2
120
30
TYP
3.92
1.5
MAX
100
UNIT
With 5% distortion and with 150 Ω
Maximum output swing
Vpp
(EARP – EARN)
With 5% distortion and with 33 Ω
Output swing 3.9Vpp
150
33
Ω
Ω
Minimum output resistive load at EARP_EARN
Output swing 1.5Vpp
Maximum output capacitive load at EARP_EARN
Earphone amplifier gain
pF
dB
0
Hi-Z
1.96
1.2
Earphone amplifier state in power down
Maximum output swing (AUXO), 5% distortion, maximum
Minimum output resistive load at AUXO
Maximum output capacitive load at AUXO
Auxo amplifier gain
Load = 1 kΩ
1.6
1.0
Vpeak
kΩ
AC coupled
100
pF
–6
Hi-Z
0
dB
Auxo amplifier state in power down
VOLCTL code = 010
–1
–7
1
VOLCTL code = 110
–6
–5
VOLCTL code = 000 (default & reference)
VOLCTL code = 100
–12
–18
–24
Volume control gains
dB
–19
–25
–17
–23
VOLCTL code = 011
VOLCTL code =101 or 001 or 111 (mute)
VDLPGA code = 0000 (default) –6 dB
–40
–6.5
–5.5
–4.5
–3.7
–2.3
–1.7
–6.0
–5.0
–4.0
–3.2
–1.8
–1.2
0
–5.5
–4.5
–3.5
–2.7
–1.3
–0.7
VDLPGA code = 0001
VDLPGA code = 0010
VDLPGA code = 0011
VDLPGA code = 0100
VDLPGA code = 0101
VDLPGA code = 0110 (ref.)
VDLPGA code = 0111
VDLPGA code = 1000
VDLPGA code = 1001
VDLPGA code = 1010
VDLPGA code = 1011
VDLPGA code = 1100
–5 dB
–4 dB
–3 dB
–2 dB
–1 dB
0 dB
PGA gain steps
dB
1 dB
0.5
1.4
2.6
3.4
4.3
5.5
1.0
1.5
2.4
3.6
4.4
5.3
6.5
2 dB
1.9
3 dB
3.1
4 dB
3.9
5 dB
4.8
6 dB
6.0
VDLST code = 1101
VDLST code = 1100
VDLST code = 0110
VDLST code = 0010
VDLST code = 0111
VDLST code = 0011
VDLST code = 0000 (ref.)
VDLST code = 0100
VDLST code = 0001
VDLST code = 1000
In the band
–23 dB
–20 dB
–17 dB
–14 dB
–11 dB
–8 dB
–5 dB
–2 dB
1 dB
–24.6 –24.1 –22.6
–21.1 –20.6 –18.5
–18.3 –17.8 –17.3
–14.8 –14.3 –13.8
–12.3 –11.8 –11.3
Sidetone gain steps
dB
dB
–8.8
–5.9
–2.1
0.7
–8.3
–4.8
–1.6
1.2
–7.8
–4.3
–1.1
1.7
Mute
–55
60
–50
Power supply rejection, 0 Hz –100 kHz
NOTE: All parameters are given for a 150 Ω load, unless specified.
16
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TCM4400E
GSM/DCS BASEBAND AND VOICE A/D
AND D/A RF INTERFACE CIRCUIT
SLWS082A – JULY 1999 – REVISED MARCH 2000
voice downlink path (continued)
frequency response of the voiceband downlink path
PARAMETER
TEST CONDITIONS
MIN
TYP
–5.8
–3.6
–2.5
–1.4
0
MAX
–5
–2
1
UNIT
100 Hz
150 Hz
200 Hz
300 Hz
–3
–1
1
1000 Hz
2000 Hz
3000 Hz
3400 Hz
Reference point
–0.6
1
1
Frequency response (Gain relative to
reference gain at 1 kHz)
dB
–1 –0.15
–3 –0.35
–9.0
1
–6
3600 Hz
–21.0
–32.0
–60.0
–15
–28
3800 Hz
4000 Hz
>4600 Hz
psophometric SNR vs signal level of the voiceband downlink path
PARAMETER
TEST CONDITIONS
MIN
TYP
MAX
UNIT
–45 dBm0
–40 dBm0
–30 dBm0
–20 dBm0
–10 dBm0
–5 dBm0
25
30
40
42
45
42
40
35
Signal level
dB
0 dBm0
3 dBm0
Idle channel noise, 0 Hz –4 kHz
Crosstalk with the uplink path
–71
–50
dBm
dB
gain characteristics of the voiceband downlink path
PARAMETER
TEST CONDITIONS
at 0 dbm0 and 1 kHz
at –10 dbm0 and 1 kHz
MIN
–1.8
TYP
0
MAX
0.2
UNIT
Absolute gain error
dB
–11.8
–0.25
–0.25
–0.25
–10
–9.8
0.25
0.25
0.25
3 dBm0
0 dBm0
–5 dBm0
Gain tracking error. Over the range 3 dBm0 to – 45 dBm0 at
1 kHz with reference –10 dBm0 PGA gain = 0dB. Volume
control = –12 dB
–10 dBm0 Reference level
–20 dBm0
0
dB
–0.25
–0.25
–0.35
–0.50
0.25
0.25
0.35
0.50
–30 dBm0
–40 dBm0
–45 dBm0
17
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TCM4400E
GSM/DCS BASEBAND AND VOICE A/D
AND D/A RF INTERFACE CIRCUIT
SLWS082A – JULY 1999 – REVISED MARCH 2000
power consumption
consumption by circuit block
CIRCUIT BLOCK
TEST CONDITIONS
MIN
TYP
MAX
UNIT
ADC
DVDD3
0.013
0.021
0.027
0.054
0.683
0.133
0.108
0.442
2.240
1.550
0.163
2.810
9.310
0.460
4.910
1.490
0.122
0.204
0.181
0.144
0.183
4.170
3.000
1.380
2.990
1.200
0.115
AFC
AGC
APC
AVDD3
AVDD5
AVDD3
AVDD5
DVDD3
AVDD3
AVDD5
AVDD4
AVDD4
AVDD1
DVDD2
AVDD2
DVDD2
AVDD2
DVDD1
DVDD1
DVDD1
DVDD1
DVDD1
DVDD4
AVDD4
AVDD4
DVDD4
AVDD4
DVDD4
AVDD4
mA
mA
mA
mA
Auxiliary input stage
Auxiliary output stage
Band gap
mA
mA
Baseband downlink
Baseband uplink
mA
BBIF
BDL Active
mA
mA
mA
mA
mA
mA
mA
mA
Clock generator BBIF
Clock generator Idle
Clock generator TIIF
Clock generator VBIF
Digital modulator
Earphone output stage
Microphone input stage
Voiceband downlink
Voiceband uplink
mA
mA
current consumption for typical configurations
PARAMETER
TEST CONDITIONS
MIN
TYP
MAX
UNIT
13-MHz clock applied; PWRDN active;
Band-gap voltage reference off
Deep power down
200
µA
Power down with AFC active
AFC + GMSK – Rx
AFCprogrammedwithinternal50-kΩ and1-MHzclock
0.7
14
19
27
1.1
16
21
30
mA
mA
mA
mA
Paging
Audio + GMSK – Tx + APC + AFC
Audio + GMSK – Rx +AGC+ AFC
Transmit burst
Receive burst
18
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TCM4400E
GSM/DCS BASEBAND AND VOICE A/D
AND D/A RF INTERFACE CIRCUIT
SLWS082A – JULY 1999 – REVISED MARCH 2000
MCU serial interface timing requirements (see Figure 3)
PARAMETER
MIN NOM
MAX
UNIT
ns
t
t
t
t
t
t
t
t
t
Setup time, UCLK stable before USEL↓
Hold time, UDX valid after USEL↓
Hold time, UDX valid after UCLK↑
20
su10
20
20
ns
v1
ns
v2
Sequential transfer delay between 16-bit word acquisition t pulse duration, USEL high
w
3000
20
ns
h9
Hold time, UCLK↑ after USEL↓
Hold time, UCLK unknown after USEL↑
Setup time, data valid before UCLK↓
Hold time, data valid after UCLK↓
Cycle time, ULCK
ns
h10
h11
su11
h12
c
20
ns
20
ns
20
ns
154
ns
DSP serial interface timing requirements (see Figure 4)
PARAMETER
MIN NOM
MAX
UNIT
BCLKX BCLKX signal frequency ( Burst mode or Continuous mode depending on bit BCLKMODE)
BCLKX BCLKX duty cycle
13
MHz
40%
20
50%
60%
t
t
t
t
Setup time, BFSX high before BCLKX ↓
Hold time, BFSX high after BCLKX ↓
Setup time, BDX valid before BCLKX ↓
Hold time, BDX valid after BCLKX ↓
ns
ns
ns
ns
su12
20
h12
20
su13
h13
20
(Output BCLKDIR = 0)
(Input BCLKDIR = 1)
4.33
50%
BCLKR BCLKR signal frequency
MHz
13
BCLKR BCLKR duty cycle
40%
20
60%
t
t
t
t
Setup time, BFSR high before BCLKR ↓
ns
ns
ns
ns
su14
Hold time, BFSR high after BCLKR ↓
Setup time, BDR valid before BCLKR ↓
Setup time, BDR valid after BCLKR ↓
20
h14
20
su16
h15
20
voice timing requirements (see Figure 5)
PARAMETER
VCLK signal frequency ( Burst mode or Continuous mode depending on bit VCLKMODE)
MIN NOM
MAX
UNIT
VCLK
VCLK
520
kHz
VCLK duty cycle
40%
100
100
100
100
100
50%
60%
t
t
t
t
t
Setup time, VFS high before VCLK ↓
Hold time, VFS high after VCLK ↓
Setup time, VDX valid before VCLK ↓
Hold time, VDX valid after VCLK ↓
Setup time, VDR valid before VCLK ↓
ns
ns
ns
ns
ns
su7
h6
su8
h8
su9
t
h7
Hold time, VDR valid after VCLK ↓
100
ns
19
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TCM4400E
GSM/DCS BASEBAND AND VOICE A/D
AND D/A RF INTERFACE CIRCUIT
SLWS082A – JULY 1999 – REVISED MARCH 2000
PARAMETER MEASUREMENT INFORMATION
uplink timing considerations
Figure 1 shows the timing diagram for the uplink operation.
Timing for power up, offset calibration, data transmission, and power ramp-up are driven by control bits applied
to BULON (base uplink on), BCAL (calibration) and BENA (enable). The burst content including guard bits, tail
bits, and data bits is sent by the DSP by way of the DSP interface and then stored by the TCM4400E in a burst
buffer. Transmission start is indicated by the control bit BENA when the BULON is active. The transmission,
sequencing, and power ramp-up are then controlled by an on-chip burst sequencer with a one-quarter-bit timing
accuracy. For a detailed description of the baseband in length path, see the functional description of the
baseband uplink path in the Principles of Operation section.
BULON
t
su2
t
BCAL
BENA
w1
t
h2
t
su3
t
w2
MODULATION
APC
t
h1
t
r1
t
f1
t
su1
t
h3
Figure 1. Uplink Timing Diagram
20
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TCM4400E
GSM/DCS BASEBAND AND VOICE A/D
AND D/A RF INTERFACE CIRCUIT
SLWS082A – JULY 1999 – REVISED MARCH 2000
PARAMETER MEASUREMENT INFORMATION
downlink timing considerations
Figure 2 shows the timing diagram for downlink operation.
Timing control of the baseband downlink path is controlled by bits DLON (downlink on), BCAL (calibration) and
BENA (enable) when BDLON is active (see the topic, timing and interface). BDLON controls the power up of
the baseband downlink path, BCAL controls the start and duration of the autocalibration sequence, and BENA
controls the beginning and the duration of data transmission to the DSP, using the DSP serial interface.
The power-down sequence is controlled with two bits, the first bit (BBDLW of PWDNRG1 register) determines
whether the baseband downlink path can be powered down with external GSM receive window activation
(BDLON); the second bit (BBDLPD of PWDNRG1 register) controls the activation of the baseband downlink
path. See the topic, power-down functional description, for more details about power-down control.
BDLON
t
su4
BCAL
t
w3
t
t
h5
su5
BENA
t
w4
DATAOUT
t
t
h4
su6
Figure 2. Downlink Timing Sequence
21
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TCM4400E
GSM/DCS BASEBAND AND VOICE A/D
AND D/A RF INTERFACE CIRCUIT
SLWS082A – JULY 1999 – REVISED MARCH 2000
PARAMETER MEASUREMENT INFORMATION
microcontroller serial interface timing considerations
Figure 3 shows the timing diagram for the microcontroller serial interface.
The microcontroller serial interface is designed to be compliant with 8-bit standard synchronous serial ports.
The microcontroller operates on 16-bit words; this interface consists of four pins.
UCLK:
UDR:
UDX:
A clock provided by the microcontroller to control access to baseband, voiceband, and auxiliary
functions registers
An input terminal to control read and write access to baseband, voiceband, and auxiliary functions
registers
An output terminal to transmit data from read access of baseband, voiceband, and auxiliary
functions registers
USEL:
An input terminal to enable read and write access to baseband, voiceband, and auxiliary functions
registers through the microcontroller interface
t
h10
USEL
UCLK
t
su10
t
h11
t
c
t
h10
t
h9
t
v2
t
su11
UDR
UDX
t
t
h12
v1
Hi-Z
Hi-Z
Figure 3. Microcontroller Serial Interface Timing Waveforms
(Mode Rising Edge Without Delay)
22
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TCM4400E
GSM/DCS BASEBAND AND VOICE A/D
AND D/A RF INTERFACE CIRCUIT
SLWS082A – JULY 1999 – REVISED MARCH 2000
PARAMETER MEASUREMENT INFORMATION
DSP serial port timing considerations
Figure 4 shows the timing diagram for DSP serial port operation.
Six pins are used for the serial port interface; see Figure 14. The terminal BCLKR is an I/O port for the serial
clock used to control the reception of the data BDR. At reset BCLKR is configured as an output and the clock
frequency is set to MCLK/3 (4.333 MHz with MCLK = 13 MHz); the clock signal is running permanently. The port
BCLKR can be reconfigured as an input by programming an internal register. In this case BCLKR is provided
bytheDSPandcanruninburstmodetoreducepowerconsumption. Thereceiveframesynchronization(BFSR)
identifies the beginning of a data packet transfer on port BDR.
The transmitted serial data (BDX) is the serial data input; the transmit frame synchronization (BFSX) is used
to initiate the transmission of data. The transmit clock (BCLKX) is provided by the GSM baseband and voice
A/D and D/A converters with a frequency of MCLK. The downlink data bus (BFSX, BCLKX, BDX) can be driven
to VSS or placed in high-impedance when no data is to be transferred to the DSP. The bit BCLKDIR of the
register BCTLREG controls the direction of the BCLKR clock.
Similar to the voice serial interface, an extra clock cycle must be generated, since the last 16-bit word received
on the DSP serial interface is latched on the next two falling BCLKR edges, following the least significant bit
(LSB). As for the voice serial interface, one extra clock period is generated on the BCLKX before the first
synchronization BFSX of downlink data sequence.
BCLKX
t
t
su13
su12
t
t
h14
h13
BFSX
BDX
A15
A14
A13
A12
A3
A2
A1
A0
MSB
LSB
a. Burst-Mode Serial-Port Transmit Operation
BCLKR
t
t
su14
su15
t
t
h15
h14
BFSR
BDR
A15
A14
A13
A12
A3
A2
A1
A0
B15
B14
B13
MSB
LSB
b. Burst-Mode Serial-Port Receive Operation
Figure 4. DSP Serial Port Timings
23
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TCM4400E
GSM/DCS BASEBAND AND VOICE A/D
AND D/A RF INTERFACE CIRCUIT
SLWS082A – JULY 1999 – REVISED MARCH 2000
PARAMETER MEASUREMENT INFORMATION
voiceband serial interface timing considerations
Figure 5 shows the timing diagram for both transmit and receive voiceband serial interface operation.
The signal VCLK is the output serial clock used to control the transmission or reception of the data (see
Figure 5). The transmitted serial data (VDX) is the serial data output; the frame synchronization (VFS) is used
to initiate the transfer of transmit and receive data. The received data (VDR) is the serial data input.
Each serial port includes four registers that include the data transmit register (DXR), the data receive register
(DRR), the transmit shift register (XSR), and the receive shift register (RSR).
The voice serial interface has the same structure and timing diagram as the serial interface; one extra cycle is
generated before VFS, and two extra cycles are generated after the LSB.
XLOAD and RLOAD are internal signals.
VCLK
t
t
su7
su8
h6
t
t
h8
VFS
VDX
A15
MSB
A14
A13
A12
A3
A2
A1
A0
LSB
XLOAD
DXR
Loaded
XSR
Loaded
a. Audio-Serial-Port Transmit Operation
VCLK
t
su9
t
h7
VFS
VDR
A15
A14
A13
A12
A3
A2
A1
LSB
A0
MSB
RLOAD
DDR
Loaded
b. Audio-Serial-Port Receive Operation
Figure 5. Voiceband Serial Interface Timing Waveforms
24
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TCM4400E
GSM/DCS BASEBAND AND VOICE A/D
AND D/A RF INTERFACE CIRCUIT
SLWS082A – JULY 1999 – REVISED MARCH 2000
PRINCIPLE OF OPERATION
baseband uplink path
Traditional transmit and receive terms can be confusing when describing a cellular telephone two-way
communication. This document uses the terms uplink, meaning from a user device to a remote station, and
downlink meaning from a remote station, whether earthbound or satellite, to indicate the signal-flow direction.
The modulator circuit in the baseband uplink path performs the Gaussian minimum shift keying (GMSK) in
accordance with the GSM specification 5.04. The data to be modulated flows from the DSP through the serial
interface, it is differentially encoded, and it is applied to the input of the GMSK modulator. The GMSK modulator,
implemented with digital logic and a sin/cos look-up table in ROM, generates the I and Q components (words)
with an interpolation ratio of 16.
These digital I and Q words are sampled at a 4.33 MHz rate and applied to the inputs of a pair of high-speed
8-bit DACs. The analog outputs are then processed by third-order Bessel filters to reduce image frequencies
due to sampling and to obtain a spectrum consistent with GSM specification 05.05 (see Figure 6).
MAGNITUDE
vs
FREQUENCY
0
–20
–40
–60
–80
–100
–120
6
10
6
2×10
6
3×10
6
4×10
6
5×10
6
6×10
0
Frequency – MHz
NOTE A: Conformance with GSM Rec 05.05: simulated spectrum of an infinite modulation of random data with a Blackman
Harris analysis window.
Figure 6. Typical GSM Modulation Spectrum
Full-differential buffered signals are available at ULIP, ULIN, ULQP, and ULQN. These signals are suitable for
use in the RF circuit for generating a phase-modulated signal of the form:
s(t) = A Cos (2 Pi fc t + Phi (t, alpha))
where fc is the RF carrier frequency, and Phi (t, alpha) is the phase component generated by the GMSK
modulator from the differential encoded data.
25
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TCM4400E
GSM/DCS BASEBAND AND VOICE A/D
AND D/A RF INTERFACE CIRCUIT
SLWS082A – JULY 1999 – REVISED MARCH 2000
PRINCIPLES OF OPERATION
baseband uplink path (continued)
Timing for power up, offset calibration, data transmission, and power ramp-up is driven by control bits applied
to BULON (base uplink on), BCAL (calibration) and BENA (enable) (see Figure 1). The entire content of a burst,
including guard bits, tail bits, and data bits, is sent by the DSP using the DSP interface and then stored by the
TCM4400E in a burst buffer. Transmission start is indicated by the control bit BENA when the BULON is active.
The transmission, sequencing, and power ramp-up are then controlled by an on-chip burst timing control circuit
having a one-quarter-bit timing accuracy (see Figure 7). All data related to a burst to be transmitted, such as
bit data, ramp-up & ramp-down delay programmation, have to be loaded before the rising edge of BENA.
The burst length is determined by the time during which the BENA signal is active. Effective burst length is equal
to the duration of BENA + 32 one-quarter bits. The tail of the burst is controlled internally, which means that the
modulation is maintained for 32 one-quarter bits after BENA turns off to generate the ramp-down sequence and
complete modulation.
For each burst, the power control level can be controlled by using the serial interfaces to write the power level
value into the power register of the auxiliary RF power control circuitry. The power ramp-up and ramp-down
sequences are controlled by the burst sequencer, while the shape of the power control is generated internally
by dedicated circuitry, which drives the power control 5-bit and 8-bit D/A converters.
To minimize phase error, the I and Q channel dc offset can be minimized using offset calibration. Each channel
includes an offset register in which a value corresponding to the required dc offset is stored, controlling the dc
offset of the I channel and Q channel D/A converters. This value is set by a calibration sequence. Starting and
stopping the calibration sequence is controlled by the control bit BCAL using the timing interface when BULON
is active. During the calibration sequence, the digital value of I and Q is forced to zero so that only the offset
register value drives the D/A converters, and a low-offset comparator senses the dc level at the BULIP/BULIN
and BULQP/BULQN outputs and modifies the content of the offset registers to minimize the dc offset (see
Figure 7).
Gain unbalance can be introduced between I and Q channels to allow compensation of imperfections in RF
circuits. This gain unbalance is controlled through the mean of three program bits: IQSEL,G1, and G0 of
baseband uplink register BULCTL.
The power-down function is controlled with two bits. The first bit (BBULW of the PWDNRG1 register),
determines whether the baseband uplink path can be powered down with external GSM transmit window
activation (BULON). The second bit (BBULPD of the PWDNREG1 register) controls the activation of the
baseband uplink path. For more details about power-down control, see the power-down functional description
section.
26
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TCM4400E
GSM/DCS BASEBAND AND VOICE A/D
AND D/A RF INTERFACE CIRCUIT
SLWS082A – JULY 1999 – REVISED MARCH 2000
PRINCIPLES OF OPERATION
baseband uplink path (continued)
–
+
Timing Interface
Din
Offset
Register
Burst
Register
Burst Timing
Control
Cosine
Table
8-Bit
DAC
Low-Pass
Filter
270 kHz
BULIP
BULIN
Differential
Encoder
Gaussian
Filter
Integrator
fs = 16 x 270 kHz
I/Q Gain Unbalance
Sine
Table
Low-Pass
Filter
BULQP
BULQN
8-Bit
DAC
Power
Register
Ramp-Up
Shaper
Offset
Register
–
+
To Power
Control DAC
Figure 7. Functional Structure of the Baseband Uplink Path
baseband downlink path
The baseband downlink path includes two identical circuits for processing the baseband I and Q components
generated by the RF circuits. The first stage of the downlink path is a continuous-time second-order antialiasing
filter (see Figure 8) that prevents aliasing due to sampling in the A/D converter. This filter also serves as an
adaptation stage (input impedance and common-mode level) between external-world and on-chip circuitry.
TYPICAL FREQUENCY RESPONSE OF THE
ANTIALIASING FILTER
10
0
–10
–20
–30
–40
–50
–60
–70
2
3
10
4
10
5
10
6
10
7
10
10
f – Frequency – Hz
Figure 8. Antialiasing Filter
27
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TCM4400E
GSM/DCS BASEBAND AND VOICE A/D
AND D/A RF INTERFACE CIRCUIT
SLWS082A – JULY 1999 – REVISED MARCH 2000
PRINCIPLES OF OPERATION
baseband downlink path (continued)
The antialiasing filter is followed by a third-order sigma-delta modulator that performs A/D conversion at a
sampling rate of 6.5 MHz. The A/D converter provides 3-bit words that are fed to a digital filter (see Figure 9)
that performs the decimation by a ratio of 24 to lower the sampling rate down to 270.8 KHz and the channel
separation by rejecting enough of the adjacent channels to allow the demodulation performances required by
the GSM specification. Figure 10 shows the frequency response curve for the downlink digital filter and Figure
11 shows the in-band response curve for the same digital filter.
The baseband downlink path includes an offset register in which the value representing the channel dc offset
is stored; this value is subtracted from the output of the digital filter before transmitting the digital samples to
the DSP using the serial interface. Upon reset, the offset register is loaded with 0 and updated with the BCAL
calibrating signal (see Figure 2).
The content of the offset register results from a calibration sequence. The input BDLIP is shorted with the input
BDLIN, and the input BDLQP is shorted with the input BDLQN. The digital outputs are evaluated and the values
are stored in the corresponding offset registers in accordance with the dc offset of the GSM baseband and voice
A/D and D/A downlink path. When the external autocalibration sequence is selected, the inputs BDLIP and
BDLIN and the inputs BDLQP and BDLQN remain connected to the external circuitry. The digital outputs are
evaluated, and the values stored in the corresponding offset registers take into account the dc offset of the
external circuitry.
Timing control of the baseband downlink path is controlled by bits BDLON (downlink on), BCAL (calibration),
and BENA (enable) when BDLON is active (please see timing interface section). BDLON controls the power
up of the baseband downlink path; BCAL controls the start and duration of the autocalibration sequence (which
can be internal or external depending on bit EXTCAL of PWDNRG1 register); and BENA controls the beginning
and the duration of data transmission to the DSP by using the DSP serial interface. To avoid transmission of
irrelevant data corresponding to the settling time of the digital filter, the eight first I&Q computed samples are
not sent to the DSP; first data are transmitted though the DSP interface about 30 µs after the BENA rising edge.
The power-down sequence is controlled with two bits. The first bit (BBDLW of PWDNRG1 register) determines
whether the baseband downlink path can be powered down with external GSM receive window activation
(BDLON): The second bit, BBDLPD of register PWDNRG1, controls the activation of the baseband downlink
path. Please see power-down functional description section for more details about power-down control.
Offset
Offset
Calibration
Register
SUB
Antialiasing
Filter
Sigma-Delta
Modulator
SINC
Filter
FIR
Filter
BDLIP
BDLIN
To Baseband
Serial Interface
fs1 = 6.5 MHz
fs2 = 1.08 MHz
fs3 = 270.8 kHz
BDLQP
BDLQN
Antialiasing
Filter
SINC
Filter
FIR
Filter
Sigma-Delta
Modulator
SUB
Offset
Offset
Calibration
Register
Figure 9. Functional Structure of the Baseband Downlink Path
28
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TCM4400E
GSM/DCS BASEBAND AND VOICE A/D
AND D/A RF INTERFACE CIRCUIT
SLWS082A – JULY 1999 – REVISED MARCH 2000
PRINCIPLES OF OPERATION
baseband downlink path (continued)
10
0
–10
–20
–30
–40
–50
–60
–70
–80
0
50
100
150
200
f – Frequency – kHz
Figure 10. Downlink Digital Filter Frequency Response
0.4
0.2
0
–0.2
–0.4
0
10
20
30
40
50
60
70
80
f – Frequency – kHz
Figure 11. Downlink Digital Filter In-Band Response
29
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TCM4400E
GSM/DCS BASEBAND AND VOICE A/D
AND D/A RF INTERFACE CIRCUIT
SLWS082A – JULY 1999 – REVISED MARCH 2000
PRINCIPLES OF OPERATION
auxiliary RF functions
The auxiliary RF functions include the following:
Automatic frequency control
Auxiliary analog converter (Automatic gain control)
RF power control
Monitoring
Each of these functions is discussed in the following paragraphs.
automatic frequency control (AFC)
The automatic frequency control function consists of a DAC converter optimized for high-resolution dc
conversion. The AFC digital interface includes two registers that can be written using the serial interfaces. The
content of these registers controls a 13-bit DAC, whose purpose is to correct frequency shifts of the oscillator
maintaining the master clock frequency in a 0.1 ppm range.
Optimizing the AFC function depends on the type of oscillator used and whether its sampling frequency is
programmable. This means that the lower the selected frequency the lower the resolution and power
consumption. Using a high-quality resonance oscillator filter permits the AFC circuit to operate at low frequency.
Thus, a low-cost oscillator permits operation at a higher internal frequency to ensure 13-bit resolution.
The AFC value is programmed with registers AUXAFC1, which contains the ten LSBs, and AUXAFC2, which
contains the three MSBs. The three MSBs are sent to the DAC through a shadow register the contents of which
is updated when LSBs are written in AUXAFC1, so proper operation of the AFC is ensured by writing the MSB’s
first and then the LSBs.
Internal resistance and output voltage swing selection are controlled with bit AFZ of AUXCTL2 register. Power
down is controlled with two bits: the first bit, AFCPN of AUXCTL1 register, determines whether the AFC can be
powered down from the external PWRDN terminal; the second bit, AFCPD of AUXCTL1 register, controls the
activation of the the AFC function. See the topic, power-down functional description for more details about
power-down control.
The auxiliary analog functions of the GSM baseband A/D and D/A conversions are independently powered from
the AV
external terminal.
DD5
auxiliary analog converter (automatic gain control (AGC))
The auxiliary analog converter control function includes a register which can be written to using the serial
interfaces and a 10-bit D/A converter that provides a control signal to set the gain of the RF section receive
amplifier. The 10-bit D/A converter is accessed through the internal register AUXAGC.
Power down is controlled with two bits. The first bit (AGCW of AUXCTL2 register) determines whether the AGC
can be powered down with the external GSM receive window activation (BDLON). The second bit (AGCPD of
AUXCTL2 register) controls the activation of AGC function. See the topic, power-down functional description
for more details about power-down control.
The auxiliary analog functions of the GSM baseband A/D and D/A conversions are independently powered from
the AV
external terminal.
DD5
30
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TCM4400E
GSM/DCS BASEBAND AND VOICE A/D
AND D/A RF INTERFACE CIRCUIT
SLWS082A – JULY 1999 – REVISED MARCH 2000
PRINCIPLES OF OPERATION
RF power control
The RF power control section includes a register that is written to using the serial interfaces. An 8-bit D/A
converter processes the content of this register and determines the gain of the RF section power amplifier.
The reference of the 8-bit D/A converter (accessed by register AUXAPC) is provided by the ramp-up-shaper
D/A converter, which is a 5-bit D/A converter controlled by the APCRAM registers located in random access
memory (RAM). This area of RAM contains sixty-four 10-bit words. These are read from address 0 through
address 62 during the ramp-up sequence. They are read from 63 through 1 during the ramp-down sequence
at a rate of 4 MHz when bit APCSPD is at zero or at a rate of 2 MHz when bit APCSPD is at 1. The ramp-up
parameters are obtained from the five least significant bits of the RAM words. The ramp-down parameters are
obtained from the most significant bits of the RAM words. Content of address 0 must be identical with content
of address 1. Content of address 62 must be identical with content of address 63.
This RAM is loaded once, and its content determines the shape of the ramp-up and ramp-down control signal.
This means these control signals can be adapted to the response of the power amplifier used in the RF section.
The shape and timing of ramp-up and ramp-down waveforms are independent.
Timing of the ramp-up and ramp-down sequences is controlled internally; however, programming of the delay
register allows adjusting the power-control start time in a 4-bit range in 1/4-bit steps. The contents of the delay
register are referenced to the BENA signal, which determines the beginning of the burst-signal modulation. This
feature allows adjusting the timing of the control signal versus the I and Q components within 1/4-bit accuracy
as defined in the specification GSM 05.05.
When APC is in power-down mode or when APC level is zero, the analog output is driven to V ; see
SS
Figure 12. During inactivity periods, the APC output is switched to V to give low-current consumption to the
SS
power amplifier (drain cutoff current of the RF amplifier);
BULON
BENA
Level 255
Level 1
Level 0
APC OUT
Offset = 120 mV
Figure 12. APC Output When APCMODE = 0
An offsetoftypically120mV(2Vswing)isaddedtotheAPCoutputtoensurelevelDAClinearity. BitAPCMODE
controls how this offset is added. When APCMODE is zero the APC output is given by
APCout = Shape value * ( Level value + Offset)
31
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TCM4400E
GSM/DCS BASEBAND AND VOICE A/D
AND D/A RF INTERFACE CIRCUIT
SLWS082A – JULY 1999 – REVISED MARCH 2000
PRINCIPLES OF OPERATION
RF power control (continued)
When APCMODE is one (see Figure 13) the APC output is given by formula
APCout = ( Shape value * Level value ) + Offset
BULON
BENA
Level 255
Level 1
APC OUT
Offset = 120 mV
Level 0
Figure 13. APC Output When APCMODE = 1
Power down is controlled with two bits. The first bit (APCW of AUXCTL2 register) determines whether the APC
canbepowereddownbyactivatingexternalGSMtransmitwindowactivation(BULON):Thesecondbit(APCPD
of AUXCTL2 register) controls the activation of APC function. See the topic, power-down functional description,
for more details about power-down control. The auxiliary analog functions of the GSM baseband A/D and D/A
conversions are independently powered from the AV
terminal.
DD5
monitoring
The monitoring section includes a 10-bit A/D converter and one result register that allows monitoring of five
external analog values such as the temperature and the battery voltage. The selection of the input and reading
of the control registers is done using the serial interfaces.
The selection of the input channel is done with the bits ADCCH0 – ADCCH2 of the AUXCTL1 register; the data
is read from the AUXADC register. Power down is controlled with two bits. The first bit (ADCPN of AUXCTL1
register) determines whether the A/D converter can be powered down from the external PWRDN terminal. The
second bit (ADCPD of AUXCTL1 register) controls the activation of the A/D conversion function. See the topic,
power-down functional description, for more details about power-down control.
Conversion is started with a write access to the AUXCTL1 register. During the conversion, the ADCEOC bit of
BSTATUS register stays at 1 and resets to 0 when the converted data is loaded into the AUXADC register. This
way the power consumption of the main parts of the converter is limited to the useful part of the conversion time.
32
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TCM4400E
GSM/DCS BASEBAND AND VOICE A/D
AND D/A RF INTERFACE CIRCUIT
SLWS082A – JULY 1999 – REVISED MARCH 2000
PRINCIPLES OF OPERATION
voice codec
The voice coder/decoder (codec) circuitry processes analog audio components in the uplink path and applies
this signal to the voice signal interface for eventual baseband modulation. In the downlink path, the codec
circuitrychangesvoice-componentdatareceivedfromthevoiceserialinterfaceintoanalogaudio. Thefollowing
paragraphs describe these uplink/downlink functions in more detail.
voice uplink path
The voice uplink path includes two input stages; refer to Figure 14. The first stage is a microphone amplifier,
compatible with an electret-type microphone, that contains a FET-buffer with an open-drain output, that has a
gain of typically 27 dB, and provides an external voltage of 2 V to 2.5 V to bias the microphone. The auxiliary
audio input can be used as an alternative source for a higher level speech signal. This stage performs
single-ended to differential conversion and provides a gain of 6 dB. When auxiliary audio input is used, the
microphone input is disabled and powered down. If both microphone and auxiliary amplifiers are powered up
at the same time, only the signal of the microphone amplifier will be transmitted to the voice uplink path.
The resulting fully differential signal is fed to a programmable gain amplifier that allows adjustment of the level
of the speech signal to the dynamic range of the A/D converter, which is determined by the value of the internal
voltage reference. Programmable gain can be set from –12 dB to +12 dB in 1-dB steps. It is programmed with
bits VULPG to VULPG4 of VBCTL1 register.
Analog-to-digital conversion is made with a third-order sigma-delta modulator whose sampling rate is 1 MHz.
Output of the A/D converter is fed to a speech digital filter, which performs the decimation down to 8 KHz and
band limits the signal with both low-pass and high-pass transfer functions. The speech samples are then
transmitted to the DSP, using the voice serial interface, at a rate of 8 kHz.
Programmable functions of the voice uplink path, power-up, input selection and gain are controlled by the DSP
or the MCU using the serial interfaces. The uplink voice path can be powered down with the bit VULON of the
VBCTL1 internal register.
Bias
MICBIAS
Generator
Side Tone
to Voice Downlink
Microphone
Amplifier
27 dB
MICIP
MICIN
IIR
Bandpass
Filter
SINC
Filter
To Voice
Serial Interface
PGA
+16.6 –7.4 dB
Sigma-Delta
Modulator
Auxiliary
Amplifier
6 dB
f
= 1 MHz
f
= 40 KHz
f
= 8 kHz
AUXI
s1
s2
s3
Figure 14. Uplink Path Block Diagram
33
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TCM4400E
GSM/DCS BASEBAND AND VOICE A/D
AND D/A RF INTERFACE CIRCUIT
SLWS082A – JULY 1999 – REVISED MARCH 2000
PRINCIPLES OF OPERATION
voice downlink path
The voice downlink path receives speech samples at an 8-kHz rate from the voice serial interface and converts
them to analog signals to drive the external speech transducer.
The digital speech coming from the voice serial interface is first fed to a speech-digital infinite-duration impulse
response (IIR) filter, which has two functions (see Figure 15). The first function is to interpolate the input signal
and increase the sampling rate form 8 kHz up to 1 MHz to permit D/A conversion by an oversampling digital
modulator. The second function is to band limit the speech signal, using both low-pass and high-pass transfer
functions.
The interpolated and band-limited signal is fed to a second-order sigma-delta modulator and sampled at 1 MHz
to generate a 1-bit oversampled signal that drives a 1-bit D/A converter.
Due to the oversampling conversion, the analog signal obtained at the output of the one-bit D/A converter is
mixed with high frequency noise. This noise is filtered by a switched-capacitor third-order low-pass filter and
the remaining signal is fed to a programmable gain amplifier (PGA) to adjust the volume control. Volume control
is done in 6-dB steps from 0 dB through –24 dB; in the mute state, attenuation is higher than 40 dB. A fine
adjustment of gainispossiblefrom–6to+6dBin1-dBstepstocalibratethesystem, dependingontheearphone
characteristics. This configuration is programmed using the VBCTL2 register.
The PGA output is fed to two output stages: the earphone amplifier that provides a full differential signal on the
terminals EARP/EARN and an auxiliary output amplifier that provides a single-ended signal on terminal AUXO.
Both earphone and auxiliary output amplifiers can be active at the same time. The downlink voice path can be
powered down with bit VDLON of the VBCTL2 internal register.
A side-tone path is connected between the output of the voice uplink PGA and the input of the voice downlink
PGA. This path provides seven programmable gains (+1 dB, –2dB, –5 dB, –8 dB, –11 dB, –14 dB, –17 dB,
–20 dB, –23 dB) and one mute position. Side-tone path gain can be selected by a programming bit at register
address 23.
Side-Tone
–23 to+1dB
Auxiliary
Amplifier
–6 dB
From Voice Uplink PGA
AUXO
Smoothing
Filter
Volume Count
and PGA
One-Bit DAC
Low-Pass Filter
+3 dB
Sigma_Delta
Modulator
–3 dB
Earphone
Amplifier
0 dB
SINC
Interpolation
Filter
IIR
Bandpass
Filter
EARP
EARN
From Voice
Serial Interface
0 +24 dB and
–6 +6 dB
f
= 1 MHz
f
= 40 KHz
f
= 8 KHz
s1
s2
s3
Figure 15. Downlink Path Block Diagram
34
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TCM4400E
GSM/DCS BASEBAND AND VOICE A/D
AND D/A RF INTERFACE CIRCUIT
SLWS082A – JULY 1999 – REVISED MARCH 2000
PRINCIPLES OF OPERATION
DAI interface
This digital audio interface (DAI) consists of four terminals: SSRST, SSCLK, SSDR, and SSDX. It is compatible
with the digital audio interface described in the GSM recommendation 11.10. This interface is designed to offer
minimum CPU overhead during audio tests and speech transcoding tests and to minimize the extra hardware
and the number of external terminals of the mobile system (MS). With this interface the DSP does not have to
deal with rate adaptation. In normal operation the DSP works with an 8-kHz sampling rate with a 16-bit word
format and frame synchronization, but the DAI interface works with an 8-kHz sampling rate with a 13-bit word
format without frame synchronization. The DSP (or the MCU) does not have real time constraints with SSRST,
since the reset of the internal transmitters is done automatically.
The DAI is controlled with four internal bits of VBCTL3 register:
DAION:
VDAI:
When 0, the DAI block is put in low power. When 1, the DAI block is active.
This bit controls the start of the clock SSCLK. The falling edges of SSRST automatically resets the
VDAI.
DAIMD 0/1: These two bits are used to switch the internal data path of the three types of DAI tests:
Tests of acoustic performance of the uplink/downlink voice path
Tests of speech decoder/DTX functions (downlink path)
Tests of speech encoder/DTX functions (uplink path)
In order to correctly execute these tests, the bits DAION/VULON/VDLON must be reset before starting the DAI
test. In the case of acoustic tests the following must be set with the sequence: DAION and VDAI, then VULON,
and finally VDLON. In case of vocoder tests, when the speech samples are ready to be exchanged with the
system simulator, the bits DAION and VDAI must be set at the same time.
35
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TCM4400E
GSM/DCS BASEBAND AND VOICE A/D
AND D/A RF INTERFACE CIRCUIT
SLWS082A – JULY 1999 – REVISED MARCH 2000
PRINCIPLES OF OPERATION
JTAG interface
TCM4400E provides a JTAG interface according to IEEE Std1149.1. This interface uses five dedicated IOs:
TCK (test clock), TMS (test mode select), TDI (scan input), TDO (scan output), and TRST (test reset). Inputs
TMS,TDI, and TRST contain a pullup device which makes their state high when they are not driven. Output TDO
is a 3-state output which is Hi-Z except when data are shifted between TDI and TDO. TRST input is intended
for proper initialization of the state machine test access port (TAP) and boundary scan cells. System RESET
is sent into the device through a boundary-scan register, which has to be initialized by TRST to allow the RESET
signal to be propagated into the device; a good practice should be to connect RESET and TRST terminals
together.
standard user instructions available.
NAME
BYPASS
OPCODE
11111
DESCRIPTION
Connects the by-pass register between TDI and TDO.
SAMPLE/PRELOAD
00010
Connects the boundary scan register between TDI and TDO. This mode captures a snapshot of the state
of the digital I/Os of the device.
EXTEST
00000
Connects the boundary scan register between TDI and TDO. This mode captures the state of the input
terminals and forces the state of the output pins. This mode is intended for printed-circuit board
connections testing between devices.
IDCODE
INTEST
00001
00011
Connects the identification register between TDI and TDO. This is the default configuration at reset.
Connects the boundary scan register between TDI and TDO. This mode forces the internal system input
signals via the parallel latches of the boundary register and captures internal system outputs. The mode
performs device internal tests independently of the state of its input terminals. In this mode the internal
system master clock is derived from TCK and is active in the run-test-idle state of the state machine to
allow step-by-step operation of the device.
JTAG interface scan chains description
bypass register
0
1
TDI
TDO
instruction register
0
0
0
0
0
5
4
3
2
1
TDI
TDO
identification register
0
0
1
0
0
1
0
0
0
0
0
0
0
0
0
0
0
1
0
0
1
0
1
1
1
1
1
TDI
32
31
30
29
13
28
12
27
11
26
10
25
9
24
23
7
22
6
21
20
4
19
3
18
2
17
1
0
1
0
0
0
5
16
15
14
8
TDO
36
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TCM4400E
GSM/DCS BASEBAND AND VOICE A/D
AND D/A RF INTERFACE CIRCUIT
SLWS082A – JULY 1999 – REVISED MARCH 2000
PRINCIPLES OF OPERATION
boundary scan register
PWRDN
SSCLK
OUT
SSDR
IN
SSDX
OUT
SSRST
IN
VCLK
OUT
VDR
IN
IN
CTL
TDI
VDX
OUT
VFS
OUT
RESET
IN
BFSR
IN
BCLKR
OUT
CTL
CTL
CTL
IN
BDR
IN
BDX
OUT
BCLKX
OUT
BFSX
OUT
UCLKR
IN
CTL
CTL
CTL
UCDR
IN
UCDX
OUT
UCSEL
IN
BDLON
IN
BULON
IN
BCAL
IN
BENA
IN
CTL
TDO
power-down functional description
During certain mobile activity (such as paging, conversation mode, or idle) it is possible to disable some
TCM4400E functions in order to lower the power consumption. For example, it is possible to disable the internal
functions dedicated to radio transmission during GSM-idle mode. It is also possible to disable the internal
demodulator path during transmit window.
There are three ways to control the power consumption of the internal blocks as described in the following
paragraphs.
direct control with internal register
With this method these internal blocks are powered down:
•
•
DAI GSM tests: bit DAION of register VBCTL3
Transmit and receive voice path: bit VULON of register VBCTL1 and bit VDLON of register VBCTL2
37
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TCM4400E
GSM/DCS BASEBAND AND VOICE A/D
AND D/A RF INTERFACE CIRCUIT
SLWS082A – JULY 1999 – REVISED MARCH 2000
PRINCIPLES OF OPERATION
radio window activation control
These internal blocks are powered up with the control of two bits. The first bit enables the window control of the
block activity; the second bit enables the power down.
First bit (PN):If cleared to 0, the function is powered down with the control of the corresponding GSM window
(BDLON/BULON terminal). If this first bit is set to 1, the power down is only controlled by the
second bit.
Second bit (PD): This bit is functionally associated with the first one. When this bit is loaded with 1, the function
is in power-down mode.
During transmit windows designated by the activity of the BULON terminal:
–
–
–
Automatic power control (APC): bits APCW and APCPD of register AUXCTL2 are paired.
Baseband uplink path: bits BBULW and BBULPD of register PWDNRG1 are paired.
External reference voltage buffers VMID: bits VMIDW and VMIDPD are paired.
During receive windows designated by the activity of the BDLON terminal:
–
–
Automatic gain control (AGC): bits AGCW and AGCPD of register AUXCTL2 are paired.
Baseband downlink path: bits BBDLW and BBDLPD of register PWDNRG1 are paired.
external terminal PWRDN control
These internal blocks are powered under the control of two bits. The first bit enables the external terminal
PWRDN control of the block activity, the second bit enables the power down. Terminal PWRDN is active high.
First bit (PN):
If cleared to 0, the function is powered down with the control of PWRDN terminal. If this first
bit is set to 1, the power down is only controlled by the second bit (PD).
Second bit (PD): This bit is functionally associated with the first one. When this bit is set to 1, the function is
in power-down mode.
–
–
–
–
For the digital serial interface to the DSP, bits BBSIPN and BBSIPD of register PWDNRG2 are paired.
For the timing interface, bits TIMGPN and TIMGPD of register PWDNRG2 are paired.
For the auxiliary A/D converters, bits ADCPN and ADCPD of register AUXCTL1 are paired.
For the automatic frequency control (AFC) block, bits AFCPN and AFCPD of register AUXCTL1 are
paired.
–
–
For the external reference voltage buffers MICBIAS, bits VREFPN and VREFPD of register PWDNRG2
are paired.
Fortheinternalreferenceband-gapbuffers, bitVGAPPNdetermineswhetherthebandgappowerdown
is under control of the PWRDN bit.
38
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TCM4400E
GSM/DCS BASEBAND AND VOICE A/D
AND D/A RF INTERFACE CIRCUIT
SLWS082A – JULY 1999 – REVISED MARCH 2000
PRINCIPLES OF OPERATION
DSP voiceband serial interface
Voiceband serial digital interface consists of a bidirectional serial port. Both receive and transmit operations are
double buffered, thus allowing a continuous communication stream. The serial port is fully static and, thus,
functions with any arbitrary low-clocking frequency.
The transfer mode available on this port is:
Clock frequency
520 kHz
16-bit data packet
frame synchronization
VCLK is the output serial clock used to control the transmission or reception of the data, (see Figure 5). VCLK
can run in burst mode or continuous mode, depending on the VCLKMODE bit. The transmitted serial data (VDX)
is the serial data output; the frame synchronization (VFS) is used to initiate the transfer of transmit and receive
data. The received data (VDR) is the serial data input.
Each serial port includes four registers: the data transmit register (DXR), the data receive register (DRR), the
transmit shift register (XSR), and the receive shift register (RSR).
The voice serial interface has the same structure and timing diagram as the serial interface. One extra cycle
is generated before VFS, and two extra cycles are generated after the least significant bit (see Figure 5).
39
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TCM4400E
GSM/DCS BASEBAND AND VOICE A/D
AND D/A RF INTERFACE CIRCUIT
SLWS082A – JULY 1999 – REVISED MARCH 2000
PRINCIPLES OF OPERATION
voltage references
Voltage and current generators are integrated inside the GSM converter. Some additional components are
required for the decoupling and regulation of the internal references. In addition, the internal buffers are
automatically shut down with the corresponding functions being powered down.
There are six terminals reserved for voltage references decoupling and use: VGAP, IBIAS, VREF, MICBIAS,
and VMID (see Table 1):
VGAP:
IBIAS:
VREF:
This terminal is connected to the internal band gap reference voltage. It must be externally
connected to a 0.1-µF capacitor. The band gap drives the current generator and the voltage
reference. This bandgap may be powered down by the PWRDN pin, depending on bit VGAPPN
of register PWDNRG2.
This terminal is connected to the current reference. It must be externally connected to a 100 kΩ
resistor. As this block is connected to the AFC function, the power down is controlled with similar
means. The current generator is shut down with the same bits as the band gap – one bit for the
power down selection of a hardware solution (with the external PWRDN terminal).
This terminal is connected to the internal reference voltage. It must be externally connected to a
0.1-µF capacitor. This band gap may be powered down with the control of the bits VREFPN and
VREFPD of the register PWDNRG2. This voltage reference is internally connected to three
buffers corresponding to the blocks of speech downlink, speech uplink, and GMSK downlink. The
two first blocks are powered down with the inactivity of the corresponding speech blocks. This last
block is shut down outside the radio downlink activations.
VMID:
This buffer gives the V /2 or 1.35 V common-mode output voltage of the baseband uplink path.
DD
This voltage value is selected with the SELVMID bit.
MICBIAS:
ADCMID:
This buffer is designed to drive an electret-type microphone. The output voltage can be chosen
by software (bit MICBIAS of VBCTL1 register) between the value 2 V to 2.5 V.
For decoupling purposes, the ADCMID terminal is connected to the internal comparison threshold
of the ADC. Setup time before the ADC is powered on is dependent on the value of the external
decoupling capacitor.
Table 1. Voltage References
REFERENCE VOLTAGE
DEFINITION
VGAP
VREF
1.22 V Band gap used for all other references
1.75 V Voltage reference of GMSK internal ADC and DAC
VMID
AV /2 Common-mode reference for uplink/downlink GMSK
DD2
MICBIAS
ADCMID
2 V / 2.5 V Microphone-driving voltage
/2 Voltage dc biasing of the auxiliary ADCs
A
VDD3
40
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TCM4400E
GSM/DCS BASEBAND AND VOICE A/D
AND D/A RF INTERFACE CIRCUIT
SLWS082A – JULY 1999 – REVISED MARCH 2000
PRINCIPLES OF OPERATION
MCU serial baseband digital interface
The GSM baseband and voice A/D and D/A conversion provide two digital serial 16-bit interfaces intended for
use with the DSP and a microcontroller device. Through this interface a microcontroller can access all the
internal registers that can be accessed through the DSP digital serial interface.
This option is intended for an application in which a part of layer-1 software is implemented into the
microcontroller needs access to some functions implemented into the GSM baseband and voice A/D and D/A
conversion circuitry.
serial interface
The microcontroller serial interface is designed to be compliant with 8-bit standard synchronous serial ports.
This interface consists of four terminals (see Figure 3 for timing diagram).
UCLK:
UDR:
A clock provided by the microcontroller to GSM baseband and voice A/D and D/A conversion
AninputterminaloftheGSMbasebandandvoiceA/DandD/Acomponentsintendedforreception
of data
UDX:
An output terminal of the GSM baseband and voice A/D and D/A components intended for
transmission of data
USEL:
An input terminal of GSM baseband and voice A/D and D/A components intended for activation
of the serial interface
When USEL = V , the serial interface is deactivated and UDX is placed in a high-impedance state. A high level
DD
on USEL resets the internal serial interface; the 16-bit transfers must be completed with USEL = V
.
SS
The external MCU initiates data transfer by driving the selection terminal and sending a clock signal. For both
the GSM baseband and voice A/D and D/A components, the MCU data is shifted out of the shift registers on
one edge of the clock and latched into the shift registers on the opposite clock edge.
As a result, both controllers send and receive data simultaneously. For the MCU portion, the software
determines whether the data is meaningful or dummy data. On the GSM baseband and voice A/D and D/A
conversion portion, dummy data is data with all zeroes.
The 16-bit word data format is identical to the DSP data format. After a read-register command, there is a
sequential transfer delay between two 16-bit word acquisitions to let the internal sequencer extract the data
going from internal registers to the serial shift register.
Three internal bits control the data serial flow as follows:
•
•
•
UDIR determines whether data is transferred with MSB or LSB first.
UPOL determines the polarity of the clock.
UPHA determines the insertion of a half-clock period in the data serial flow.
With UPOL and UPHA there are four clock schemes (see Table 2):
•
•
•
•
Falling edge without delay. The MCU serial interface transmits data on the falling edge of the UCLK and
receives data on the rising edge of the UCLK.
Falling edge with delay. The MCU serial interface transmits data one half-cycle ahead of the fallingedge
of the UCLK and receives data on the falling edge of the UCLK.
Rising edge without delay. The MCU serial interface transmits data on the rising edge of the UCLK and
receives data on the falling edge of the UCLK.
Rising edge with delay. The MCU serial interface transmits data one half-cycle ahead of the rising edge
of the UCLK and receives data on the rising edge of the UCLK.
41
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TCM4400E
GSM/DCS BASEBAND AND VOICE A/D
AND D/A RF INTERFACE CIRCUIT
SLWS082A – JULY 1999 – REVISED MARCH 2000
PRINCIPLES OF OPERATION
serial interface (continued)
Table 2. Microcontroller Clocking Schemes
UPOL
UPHA
MCU CLOCKING SCHEME
Falling edge without delay
Falling edge with delay
1
1
0
0
1
0
1
0
Rising edge without delay
Rising edge with delay
DSP/MCU serial interface
The DSP/MCU serial interface not only configures the GSM baseboard and voice A/D and D/A conversion but
alsotransmitsdatatotheDSPduringdownlinkburstreactions. Thefollowingparagraphsdescribetheoperation
of the serial interface in more detail.
DSP serial digital interface
The DSP serial digital interface (Figure 16) is used to transfer the baseband transmit and receive data, and it
is also used to access all internal programming registers of the device (baseband codec, voice codec, and
auxiliary RF functions). The format for the serial interface is 16 bits.
The baseband serial digital interface is a bidirectional (transmit/receive) serial port. Both receive and transmit
operations are double buffered and permit a continuous communication stream (16-bit data packets). The serial
port is fully static and functions with any arbitrary, low-clocking frequency.
Six terminals are used for the serial port interface (see Figure 4 for timing diagram). BCLKR is an I/O port for
the serial clock used to control the reception of the data BDR. At reset BCLKR is configured as an output and
the clock frequency is set to MCLK/3 (4.333 MHz with MCLK = 13 MHz); the clock signal is running permanently.
The port BCLKR can be reconfigured as an input by programming an internal register. In this case BCLKR is
provided by the DSP. It can run in burst mode to reduce power consumption. The receive frame synchronization
(BFSR) is used to identify the beginning of a data packet transfer on port BDR.
The transmitted serial data (BDX) is the serial data input; the transmit frame synchronization (BFSX) is used
to initiate the transmission of data. The transmit clock (BCLKX) is provided by the GSM baseband and voice
A/D and D/A converters with a MCLK frequency. The clock signal BCLKX can run in burst mode or continuous
mode, depending on the BCLKMODE bit. The downlink data bus (BFSX, BCLKX, BDX) can be driven to VSS
or placed in a high-impedance state when no data is to be transferred to the DSP. The BCLKDIR bit of the
BCTLREG register controls the direction of the BCLKR clock.
As with the voice serial interface, on extra clock cycle must be generated because the last 16-bit word received
on the DSP serial interface is latched on the next two falling BCLKR edges following the LSB. As for the voice
serial interface, one extra clock period is generated on the BCLKX before the first synchronization BFSX of the
downlink data sequence.
42
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TCM4400E
GSM/DCS BASEBAND AND VOICE A/D
AND D/A RF INTERFACE CIRCUIT
SLWS082A – JULY 1999 – REVISED MARCH 2000
PRINCIPLES OF OPERATION
Data Bus
16
16
Load
Load
DRR
DXR
Control
Logic
Control
Logic
16
16
RSR
XSR
Clear
Clock
Clear
Clock
Byte/Word
Counter
Byte/Word
Counter
BDR
BFSR BCLKR BCLKX BFSX
BDX
Figure 16. DSP Serial Digital Interface
timing interface
The timing interface performs accurate timing control of baseband uplink and downlink paths. The timing
interface is a parallel asynchronous port with four control signals, refer to Figure 17. The BDLON bit controls
power on the downlink path of the baseband codec; the BULON bit controls power on the uplink path of the
baseband codec, and the BCAL bit controls the calibration of the active parts of the baseband codec selected
by BULON or BDLON.
The BENA bit controls the transmission of the reception of burst depending on which part of the baseband codec
is selected by the signals BULON or BDLON. These asynchronous inputs are internally synchronized with the
uplink and downlink internal clocks and stored in timing register TR. The timing register, TR, is a 6-bit register
containing the bits defined in Table 3.
Table 3. 6-Bit TR Register
BIT5
BIT4
BIT3
BIT2
BIT1
BIT0
ULON
ULCAL
ULSEND
DLON
DLCAL DLREC
TR bit signification
ULON:
Ifsetto1, thisbitturnsontheuplinkpathofthebasebandcodec;ifclearedto0, theuplinkpath
is in power-down mode.
ULCAL:
When this bit is set to 1, the uplink offset autocalibration is active.
ULSEND:
A transition from 0 to 1 of ULSEND initiates the emission of a burst. The burst information
data, burst length, and power level need to be loaded in the corresponding registers using the
serial interface.
DLON:
If set at 1, this bit turns on the downlink path of the baseband codec; if cleared to 0, the
downlink path is in power-down mode.
DLCAL:
DLREC:
When this bit is set at 1, the downlink offset autocalibration is active.
A transition from 0 to 1 of DLREC initiates the transmission of data from the baseband codec
to the DSP using the serial interface.
43
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TCM4400E
GSM/DCS BASEBAND AND VOICE A/D
AND D/A RF INTERFACE CIRCUIT
SLWS082A – JULY 1999 – REVISED MARCH 2000
PRINCIPLES OF OPERATION
BDLON
BCAL BULON
BENA
CKDL
CKUL
DLON DLCAL DLREC ULON ULCAL ULSEND
Figure 17. Timing Interface
DSP/MCU serial interface operation and format
The DSP/MCU serial interface configures the GSM baseband, the voice A/D and D/A converters (read and write
operation in internal registers), and transmits RF data to the DSP during the reception of a burst by the downlink
path of the GSM baseband and voice A/D and D/A circuitry.
During reception of a burst (bit DLR of the status register is 1) and DSP serial interface and associated internal
bus are dedicated to the transfer of RF data from the GSM baseband A/D and D/A converters to the DSP. During
this period only a write operation of internal registers can be done through the DSP serial interface. However,
all registers can be accessed by the serial MCU interface.
During transmission of a burst (bit ULX of the status register is 1) no read or write operation can be done in the
registers of the baseband uplink part of the GSM baseband, APC RAM, and APC shape register.
Writing or reading registers using the serial interface is done by transferring 16-bit words to the serial interface.
Each word is split into three fields as shown in Table 4.
Table 4. Read/Write Data Word
DATA
10
ADDRESS
R/W
15
14
13
12
11
9
8
7
6
5
4
3
2
1
1 / 0
When writing to internal registers observe the following convention:
Bit 0
: A 0 indicates a write operation.
: This field contains the address of the register to be accessed.
Bits 1 to 5
Bits 6 to 15 : This field contains the data to be written into the internal register.
When reading from internal registers observe the following convention:
Bit 0
: A 1 indicates a read operation.
Bits 1 to 5
: This field contains the address of the register to be accessed.
Bits 6 to 15 : This field is an irrelevant status in a read request operation.
44
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TCM4400E
GSM/DCS BASEBAND AND VOICE A/D
AND D/A RF INTERFACE CIRCUIT
SLWS082A – JULY 1999 – REVISED MARCH 2000
PRINCIPLES OF OPERATION
Read operation from the downlink baseband codec is done using the TX part of the DSP/MCU serial interface
in the following 16-bit word format given in Table 5.
Table 5. 16-Bit Word Format
DATA
10
D4
ADDRESS
15
14
13
12
11
9
8
7
6
5
4
3
2
1
0
0
D9
D8
D7
D6
D5
D3
D2
D1
D0
A4
A3
A2
A1
A0
During reception of a burst, transfer of RF data from the downlink baseband codec is done using the transmit
part of the DSP serial interface in the following 16-bit word format: As the I and Q samples are coded with 16-bit
words, the data rate is 270833 × 16 × 2 which equals 8.66 Mbps. I & Q samples are differentiated by setting the
LSB to zero for I samples and to one for Q samples. Since the digital clock MCLK is 13 MHz, transfer is done
at 13 Mbps in burst mode. During burst reception the DSP serial interface is idled about 33% of the time.
Table 6. Format of 16-Bit Word Transfer
DATA
8
I/Q
0
15
14
13
12
11
10
9
7
6
5
4
3
2
1
D15
D14
D13
D12
D11
D10
D9
D8
D7
D6
D5
D4
D3
D2
D1
D0
DSP/MCU serial interface registers
The following internal register buffers are accessed using the DSP/MCU serial interface during manual
operation of the TCM4400E.
baseband uplink ramp delay register
Each bit position of the baseband uplink ramp-delay register is given in Table 7.
Table 7. Uplink Ramp-Delay Register
BULRUDEL: BASEBAND UPLINK RAMP DELAY REG.
ADDRESS: 1
R/W
RESERVD
IBUFPTR DELD3 DELD2 DELD1 DELD0 DELU3 DELU2 DELU1 DELU0
0
0
0
0
1
1 / 0
R = 0
0
R/W
0
R/W
0
R/W
0
R/W
0
R/W
0
R/W
0
R/W
0
R/W
0
R/W
0
<––– ACCESS TYPE
<–––VALUE AT RESET
DELU0 to DELU3
DELD0 to DELD3
IBUFPTR
: Value of the delay of ramp-up start versus the rising edge of BENA
: Value of the delay of ramp-down start versus the falling edge of BENA
: Writing a 1 in this bit initializes the pointer of the burst buffer to the base address.
(This is not a toggle bit and has to be set back to 0 to allow writing into the burst
buffer).
RESERVD
R/W
: Reserved bits for testing purposes
: A 1 indicates a read operation; a 0 indicates a write operation.
45
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TCM4400E
GSM/DCS BASEBAND AND VOICE A/D
AND D/A RF INTERFACE CIRCUIT
SLWS082A – JULY 1999 – REVISED MARCH 2000
PRINCIPLES OF OPERATION
baseband uplink data buffer
The baseband uplink data buffer is used to transmit the uplink burst data. The uplink data buffer contents are
shown in Table 8.
Table 8. Uplink Data Buffer
BULDATA: BASEBAND UPLINK DATA BUFFER
ADDRESS: 2 (16 WORDS)
W
0
0
0
0
0
0
0
0
0
0
0
0
0
0
0
0
BIT0
BIT1
BIT2
BIT3
BIT4
BIT5
BIT6
BIT7
BIT8
BIT9
0
0
0
0
0
0
0
0
0
0
0
0
0
0
0
0
0
0
0
0
0
0
0
0
0
0
0
0
0
0
0
0
0
0
0
0
0
0
0
0
0
0
0
0
0
0
0
0
1
1
1
1
1
1
1
1
1
1
1
1
1
1
1
1
0
0
0
0
0
0
0
0
0
0
0
0
0
0
0
0
BIT10
BIT20
BIT30
BIT40
BIT50
BIT60
BIT70
BIT80
BIT90
BIT11
BIT21
BIT31
BIT41
BIT51
BIT61
BIT71
BIT81
BIT91
BIT12
BIT22
BIT32
BIT42
BIT52
BIT62
BIT72
BIT82
BIT92
BIT13
BIT23
BIT33
BIT43
BIT53
BIT63
BIT73
BIT83
BIT93
BIT14
BIT24
BIT34
BIT44
BIT54
BIT64
BIT74
BIT84
BIT94
BIT15
BIT25
BIT35
BIT45
BIT55
BIT65
BIT75
BIT85
BIT95
BIT16
BIT26
BIT36
BIT46
BIT56
BIT66
BIT76
BIT86
BIT96
BIT17
BIT27
BIT37
BIT47
BIT57
BIT67
BIT77
BIT87
BIT97
BIT18
BIT28
BIT38
BIT48
BIT58
BIT68
BIT78
BIT88
BIT98
BIT19
BIT29
BIT39
BIT49
BIT59
BIT69
BIT79
BIT89
BIT99
BIT100 BIT101 BIT102 BIT103 BIT104 BIT105 BIT106 BIT107 BIT108 BIT109
BIT110 BIT111 BIT112 BIT113 BIT114 BIT115 BIT116 BIT117 BIT118 BIT119
BIT120 BIT121 BIT122 BIT123 BIT124 BIT125 BIT126 BIT127 BIT128 BIT129
BIT130 BIT131 BIT132 BIT133 BIT134 BIT135 BIT136 BIT137 BIT138 BIT139
BIT140 BIT141 BIT142 BIT143 BIT144 BIT145 BIT146 BIT147 BIT148 BIT149
BIT150 BIT151 BIT152 BIT153 BIT154 BIT155 BIT156 BIT157 BIT158 BIT159
W
1
W
1
W
1
W
1
W
1
W
1
W
1
W
1
W
1
W
1
<–––ACCESS TYPE
<–––VALUE AT RESET
Bit 0 – Bit 159 are the bits composing the sequence of the transmitted burst, bit 0 is transmitted first. For a normal
burst, the uplink data buffer is loaded as follows:
Bit 0 to 3
: 4 guard bits
Bit 4 to 6
: 3 tail bits
Bit 7 to 66
Bit 67 to 92
Bit 93 to 92
: 58 data bits
: 26 training sequence bits
: 58 training sequence bits
Bit 151 to 153 : 3 tail bits
Bit 154 to 159 : 8 guard bits
At reset and after each transmission, the burst buffer is reinitialized with guard bits (all bits = 1). An address
pointer is incremented after each word written into the buffer so that next write operation affects the next word
of the buffer. This address pointer is set to the base address (Word 0) by a RESET, after transmission of a burst
or by setting the IBUFPTR bit to 1( this bit has to be set back to zero to release the address pointer).
46
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TCM4400E
GSM/DCS BASEBAND AND VOICE A/D
AND D/A RF INTERFACE CIRCUIT
SLWS082A – JULY 1999 – REVISED MARCH 2000
PRINCIPLES OF OPERATION
baseband uplink I and Q offset registers
The baseband uplink I and Q offset registers contain the offset values for the I and Q components, respectively,
as shown in Tables 9 and 10.
Table 9. Uplink I Offset Register
BULIOFF: BASEBAND UPLINK I OFFSET REGISTER
ADDRESS: 3 R/W
1/0
<–ACCESS TYPE
<–VALUE AT RESET
RESERVD ULIOFF8 ULIOFF7 ULIOFF6 ULIOFF5 ULIOFF4 ULIOFF3 ULIOFF2 ULIOFF1 ULIOFF
0 0 0 1 1
R
0
R/W
0
R/W
1
R/W
1
R/W
1
R/W
1
R/W
1
R/W
1
R/W
1
R/W
1
ULIOFF0 to ULIOFF1 : Integration bits during calibration (to minimize sensitivity to noise)
ULIOFF2 to ULIOFF8 : Value of the offset on I channel
RESERVD
R/W
: Reserved bits for testing purposes
: A 1 indicates a read operation; a 0 indicates a write operation.
Table 10. Uplink Q Offset Register
BULQOFF: BASEBAND UPLINK Q OFFSET REGISTER
ADDRESS: 4
R/W
RESERVD ULQOFF8 ULQOFF7 ULQOFF6 ULQOFF5 ULQOFF4 ULQOFF3 ULQOFF2 ULQOFF1 ULQOFF0
0
0
1
0
0
1/0
R
0
R/W
0
R/W
1
R/W
1
R/W
1
R/W
1
R/W
1
R/W
1
R/W
1
R/W
1
<–ACCESS TYPE
<–VALUE AT RESET
ULQOFF0 to ULQOFF1: Integration bits during calibration (to minimize sensitivity to noise)
ULQOFF2 to ULQOFF8: Value of the offset on Q channel
RESERVD
R/W
: Reserved bits for testing purposes
: A 1 indicates a read operation; a 0 indicates a write operation.
baseband uplink I and Q D/A conversion registers
The I and Q component values generated by the I and Q uplink D/A converter during the conversion of analog
data are written to and read from the uplink I and Q D/A converter registers as shown in Tables 11 and 12.
Table 11. Uplink I DAC Register
BULIDAC: BASEBAND UPLINK I DAC REGISTER
ADDRESS: 6 R/W
RESERVD
RESERVD
RESERVD
RESERVD
RESERVD
RESERVD
RESERVD
RESERVD
RESERVD
RESERVD
0
0
1
1
0
1/0
R
0
R
0
R
0
R
0
R
0
R
0
R
0
R
0
R
0
R
0
<–ACCE0S TYPE
<–VALUE AT RESET
RESERVD
: Reserved bits for testing purposes
47
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TCM4400E
GSM/DCS BASEBAND AND VOICE A/D
AND D/A RF INTERFACE CIRCUIT
SLWS082A – JULY 1999 – REVISED MARCH 2000
PRINCIPLES OF OPERATION
Table 12. Uplink Q DAC Register
BULQDAC: BASEBAND UPLINK Q DAC REGISTER
ADDRESS: 5 R/W
RESERVD
RESERVD
RESERVD
RESERVD
RESERVD
RESERVD
RESERVD
RESERVD
RESERVD
RESERVD
0
0
1
0
0
1/0
R
0
R
0
R
0
R
1
R
1
R
1
R
1
R
1
R
1
R
1
<–ACCE0S TYPE
<–VALUE AT RESET
RESERVD
: Reserved bits for testing purposes
Power down register No. 2
The values in each bit position of power-down register No. 2 have the meaning outlined in Table 13.
Table 13. PWDNRG2 Register
PWDNRG2: REGISTER FOR POWERING DOWN
ADDRESS: 8 R/W
RESERVD RESERVD
TIMGPN
R/W
0
TIMGPD
R/W
0
BBSIPN
R/W
0
BBSIPD
R/W
0
VGAPPN
R/W
0
CHGUP
R/W
0
VREFPN
R/W
0
VREFPD
R/W
0
0
1
0
0
0
1/0
R = 0
0
R = 0
0
<–ACCESS TYPE
<–VALUE AT RESET
VREFPN: If cleared to 0, the internal reference voltage is powered down under the control of terminal
PWRDN and bit VREFPD. If bit VREFPN is set to 1, the power down is only controlled by bit
VREFPD.
VREFPD: This bit is functionally associated with bit VREFPN.
VGAPPN: If cleared to 0, the internal reference VGAP is powered down under the control of terminal
PWRDN. If this bit is set to 1, the VGAP is not placed in power-down mode.
TIMGPN: If cleared to 0, the internal reference VGAP is powered down under the control of terminal
PWRDN. If this bit is set to 1, the power-down control is only controlled by bit TIMPGD
TIMGPD: This bit is functionally associated with bit TIMGPN.
BBSIPN: If cleared to 0, the baseband serial interface is powered down under the control of terminal
PWRDN. If this bit is set to 1, the power down is only controlled by bit BBSIPD.
BBSIPD: This bit is functionally associated with bit BBSIPN. When this bit is set to 1, baseband serial
interface is in power-down mode.
CHGUP: This bit is used for testing purposes to accelerate the bandgap settling time.
RESRVD: Reserved bits for testing purpose
48
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TCM4400E
GSM/DCS BASEBAND AND VOICE A/D
AND D/A RF INTERFACE CIRCUIT
SLWS082A – JULY 1999 – REVISED MARCH 2000
PRINCIPLES OF OPERATION
power down register No. 1
The values in each bit position of power down register No. 1 have the meaning outlined in Table 14.
Table 14. PWDNRG1 Register
PWDNRG1: REGISTER FOR POWERING DOWN
ADDRESS: 7 R/W
SELVMID
R/W
0
BALOOP
R/W
0
VMIDW
R/W
0
VMIDPD
R/W
0
BBULW
R/W
0
BBULPD
R/W
0
BBDLW
R/W
0
BBDLPD
R/W
0
EXTCAL
R/W
0
BBRST
R/W
0
0
0
1
1
1
1/0
<–ACCESS TYPE
<–VALUE AT RESET
BBRST:
This is the digital reset of the baseband codec (active at 1); the uplink burst buffer is loaded with
all 1s and the memory and registers of the downlink digital filter is cleared to 0. This is not a
toggle bit as it has to be set to 0 to remove the reset condition.
EXTCAL: Downlink autocalibration mode (at 0: autocalibration; at 1: external calibration)
BBULW:
Ifclearedto0, thebasebanduplinkpathispowereddownunderthecontroloftheGSMtransmit
window (BULON terminal). If this bit is set to 1, the power down is only controlled by bit
BBULPD.
BBULPD: This bit is functionally associated with bit BBULW. When this bit is set to 1, the baseband uplink
path is in power-down mode.
BBDLW:
If cleared to 0, the baseband downlink path is powered down under the control of GSM receive
window (BDLON terminal). If this bit is set to 1, the power down is only controlled by bit
BBDLPD.
BBDLPD: This bit is functionally associated with bit BBDLW. When this bit is set to 1, the baseband
downlink path is in power-down mode.
VMIDW:
If cleared to 0, the VMID output driver is powered down under the control of GSM transmit
window (BULON terminal). If this bit is set to 1, the power down is only controlled by bit
VMIDPD.
VMIDPD: This bit is functionally associated and paired with bit VMIDW. When VMIDW bit is set to 1, the
VMID output driver is active. When VMIDPD bit is set to 1, the VMID output driver is in
power-down mode.
BALOOP: When set to 1, the internal analog loop of I and Q uplink terminals are connected to I and Q
downlink terminals.
SELVMID: When cleared to 0, this sets the common-mode voltage of the baseband uplink and VMID at
V
/2; when set to 1, these voltages are set to 1.35 V.
DD
49
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TCM4400E
GSM/DCS BASEBAND AND VOICE A/D
AND D/A RF INTERFACE CIRCUIT
SLWS082A – JULY 1999 – REVISED MARCH 2000
PRINCIPLES OF OPERATION
baseband control register (see Table 15)
The values in the baseband control register bit positions determine whether the data is shifted left or right. Note
that the microcontroller unit (MCU) clocking scheme determines on which edge of the clock that data is received
or transmitted using the serial interface.
Table 15. Baseband Control Register
BCTLREG: BASEBAND CONTROL REGISTER
ADDRESS: 9
R/W
RESERVD RESERVD RESERVD MCLKBP BCLKMODE BIZBUS
BCLKDIR
R/W
0
UDIR
R/W
0
UPHA
R/W
0
UPOL
R/W
0
0
1
0
0
1
1/0
R = 0
0
R = 0
0
R = 0
0
R /W
0
R /W
0
R/W
0
<–ACCESS TYPE
<–VALUE AT RESET
UDIR:
This bit determines whether the data is shifted in from right (see serial register description) to
left, MSB first (bit value 0), or from left to right, LSB first (bit value 1).
BCLKMODE:When cleared to 0, BLCKX runs in the burst mode; when set to 1, BCLKX is continuous.
MCLKBP:
Whenclearedto0, MCLKsignalpassesthroughtheclockslicer;whensetto1, theclockslicer
is bypassed (in this case, the signal at the MCLK terminal must be digital).
MCU clocking schemes
Falling edge without delay: The MCU serial interface transmits data on the falling edge of the UCLK and
receives data on the rising edge of UCLK.
Falling edge with delay:
TheMCUserialinterfacetransmitsdataonehalf-cycleaheadofthefallingedge
of the UCLK and receives data on the falling edge of the UCLK.
Rising edge without delay: The MCU serial interface transmits data on the rising edge of the UCLK and
receives data on the falling edge of the UCLK.
Rising edge with delay:
The MCU serial interface transmits data one half-cycle ahead of the rising edge
of the UCLK and receives data on the rising edge of UCLK.
Table 16. MCU Clocking Schemes
UPOL
UPHA
MCU CLOCKING SCHEME
Falling edge without delay
1
1
0
0
1
0
1
0
Falling edge with delay
Rising edge without delay
Rising edge with delay
BCLKDIR: Direction of the BCLKR port ( 0 –> Output, 1–> Input).
BIZBUS:
When set to 1, BDX, BCLKX, BFSX are in hi-Z when there is nothing to transfer to the DSP;
when cleared to 0, DBX, BCLKX, BFSX are set to V when there is nothing to transfer to the
SS
DSP.
RESRVD:
Reserved bits for testing purpose
50
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TCM4400E
GSM/DCS BASEBAND AND VOICE A/D
AND D/A RF INTERFACE CIRCUIT
SLWS082A – JULY 1999 – REVISED MARCH 2000
PRINCIPLES OF OPERATION
voiceband uplink control register
The values in the voiceband uplink control register bit positions control not only the power level of the audio in
the uplink path but also set the gain of the PGA from –12 dB to 12 dB in 1 dB steps. Bit MICBIAS and VULMIC
and VULAUX are shifted by one position to the left. This is shown in Table 17.
Table 17. Voiceband Uplink Control Register
VBCTL1: VOICEBAND UPLINK CONTROL REGISTER
ADDRESS: 10 R/W
VDXMUTE
MICBIAS
R /W
0
VULMIC
R/W
0
VULAUX
R/W
0
VULPG4
R/W
0
VULPG3
R/W
0
VULPG2
R/W
0
VULPG1
R/W
0
VULPG0
R/W
0
VULON
R/W
0
0
1
0
1
0
1/0
R/W
0
<–ACCESS TYPE
<–VALUE AT RESET
VULON:
Power on the uplink path of the audio codec
VULAUX:
VULMICL:
MICBIAS:
Enables the auxiliary input amplifier if bit VULON is 1
Enables the microphone input amplifier if bit VULON is 1
When MICBIAS = 0, the analog bias for the electret-type microphone and external
decoupling is driven to 2 V; when the value is 1, the bias is 2.5 V.
VDXMUTE:
When VDXMUTE = 1, the VDX output is forced to zero, when the value is 0, VDX is
transmitted normally. To avoid cutting a VDX word during transmission due to
asynchronism of writing this bit via DSP or MCU serial interface, VDXMUTE is internally
resynchronized with the 8 KHz voice frame.
VULPG (0–4):
Gain of the voice uplink programmable gain amplifier (–12 dB to 12 dB in 1 dB step), see
Table 18.
51
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TCM4400E
GSM/DCS BASEBAND AND VOICE A/D
AND D/A RF INTERFACE CIRCUIT
SLWS082A – JULY 1999 – REVISED MARCH 2000
PRINCIPLES OF OPERATION
Table 18. Uplink PGA Gain
VULPG 4 VULPG 3 VULPG 2 VULPG 1 VULPG 0
RELATIVE GAIN
–12 dB
–11 dB
–10 dB
–9 dB
–8 dB
–7 dB
–6 dB
–5 dB
–4 dB
–3 dB
–2 dB
–1 dB
0 dB
1
1
1
1
1
1
0
0
0
0
0
0
0
0
0
0
0
0
0
1
1
1
1
1
1
0
0
1
1
1
1
0
0
0
0
0
0
0
0
1
1
1
1
1
0
0
0
0
0
0
0
1
0
0
0
0
0
0
0
0
1
1
1
1
0
0
0
0
1
0
0
0
1
1
1
0
1
0
0
1
1
0
0
1
1
0
0
1
1
0
0
1
1
0
0
1
1
0
0
1
0
1
0
1
0
1
0
1
0
1
0
1
0
1
0
1
0
1
0
1
0
1
0
1
0
1 dB
2 dB
3 dB
4 dB
5 dB
6 dB
7 dB
8 dB
9 dB
10 dB
11 dB
12 dB
voiceband downlink control register
The values in the voiceband downlink control register bit positions control the audio power level in the downlink
path. Earphone volume is set (three bits VOLCTL0 –VOLCTL2) and PGA gain is set from –6 dB to 6 dB in 1
dB steps. This is shown in Table 19.
Table 19. Voiceband Downlink Control Register
VBCTL2: VOICEBAND DOWNLINK CONTROL REGISTER
ADDRESS: 11 R/W
VDLAUX
R/W
0
VDLEAR
R/W
0
VOLCTL2
R/W
0
VOLCTL1
R/W
0
VOLCTL0
R/W
0
VDLG3
R/W
0
VDLG2
R/W
0
VDLG1
R/W
0
VDLG0
R/W
0
VDLON
R/W
0
0
1
0
1
1
1 / 0
<–ACCESS TYPE
<–VALUE AT RESET
VDLON:
VDLEAR:
VDLAUX:
Power on of the downlink path of the audio codec
Enables the earphone amplifier if the VDLON bit is 1
Enables the auxiliary output amplifier if the VDLON bit is 1
VGLG (0–3) 1 dB:
Gainofthevoice-downlinkprogrammablegainamplifier(–6dBto6dBin1-dBsteps);
see Table 20.
52
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TCM4400E
GSM/DCS BASEBAND AND VOICE A/D
AND D/A RF INTERFACE CIRCUIT
SLWS082A – JULY 1999 – REVISED MARCH 2000
PRINCIPLES OF OPERATION
Table 20. Downlink PGA Gain
VDLG3 VDLG2 VDLG1 VDLG0 RELATIVE GAIN
0
1
0
0
0
0
0
0
0
0
1
1
1
1
1
1
1
1
0
0
0
0
1
1
1
1
0
0
0
0
1
1
1
1
0
0
1
1
0
0
1
1
0
0
1
1
0
0
1
1
0
1
0
1
0
1
0
1
0
1
0
1
0
1
0
1
–6 dB
–5 dB
–4 dB
–3 dB
–2 dB
–1 dB
0 dB
2
3
4
5
6
7
1 dB
8
2 dB
9
3 dB
10
11
12
13
14
15
4 dB
5 dB
6 dB
–6 dB
–6 dB
–6 dB
VOLCTL (0–2):
Volume control (0, –6 ,–12, 18, –24, Mute), see Table 21.
Table 21. Volume Control Gain Settings
VOLCTL2 VOLCTL1 VOLCTL0 RELATIVE GAIN
0
1
2
3
4
5
6
7
0
1
0
1
0
1
0
1
1
1
0
0
1
0
0
1
0
0
0
0
1
1
1
1
0 dB
–6 dB
–12 dB
–18 dB
–24 dB
Mute
Mute
Mute
53
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TCM4400E
GSM/DCS BASEBAND AND VOICE A/D
AND D/A RF INTERFACE CIRCUIT
SLWS082A – JULY 1999 – REVISED MARCH 2000
PRINCIPLES OF OPERATION
voiceband control register
The values in the voiceband control register have the meaning shown in Table 22.
Table 22. Voiceband Control Register
VBCTL3: VOICEBAND CONTROL REGISTER
ADDRESS: 12 R/W
RESERVD RESERVD VCLKMODE
DAIMD1
R/W
0
DAIMD0
R/W
0
VDAI
R/W
0
DAION
R/W
0
VALOOP
R/W
0
VIZBUS
R/W
0
VRST
R/W
0
0
1
1
0
0
1 / 0
R = 0
0
R = 0
0
R /W
0
<–ACCESS TYPE
<–VALUE AT RESET
VALOOP:
When set to 1, the internal analog loop of output samples are sent to the audio input
terminal; standard audio paths are connected together, and auxiliary audio paths are
connected together.
VIZBUS:
When set to 1, VFS, VCLK, and VDX are put in a hi-Z state when there is nothing to transfer
to the DSP. When cleared to 0, VFS and VCLK are put in V when there is nothing to
SS
transfer to the DSP, and the VDX bus drives an undefined value (value depends on the
previous serial data transfers).
VRST:
When1, resetsthedigitalpartsoftheaudiocodec(digitalfilterandmodulator). Thisisnota
toggle bit and has to be set to 0 to remove the reset condition
DAION:
VDAI:
When cleared to 0, the DAI block is in power down; when set to 1, the DAI block is active.
Writing a 1 to this bit starts the SSCLK (104 kHz DAI clock) on reception of the first sample.
This bit is automatically reset to 0 by SSRST after reception of the last sample.
RESERVD:
Reserved bits for testing
DAIMD (0–1): DAI mode selection as given in Table 23.
VCLKMODE: When cleared to 0, allows selection of VCLK in burst mode. When set to 1, allows selection
of VCLK in continuous mode.
Table 23. DAI Mode Selection
DAIMD1 DAIMD0
DAI MODE
0
0
1
1
0
1
0
1
Normal operation (no tested device using DAI)
Test of speech decoder / DTX functions (downlink)
Test of speech encoder / DTX functions (uplink)
Test of acoustic devices and A/D and D/A (voice path)
54
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TCM4400E
GSM/DCS BASEBAND AND VOICE A/D
AND D/A RF INTERFACE CIRCUIT
SLWS082A – JULY 1999 – REVISED MARCH 2000
PRINCIPLES OF OPERATION
auxiliary functions control register 1
Thebitvaluesintheauxiliaryfunctionscontrolregister1resetstheAPCgeneratorortheAFCmodulator, selects
the A/D counter input, and selects the AFC sampling frequency. This is shown in Table 24.
Table 24. AUX Functions Control Register 1
UXCTL1: AUXILIARY FUNCTIONS CONTROL REGISTER
ADDRESS: 13 R/W
AFCPN
R/W
0
AFCPD
R/W
0
ADCPN
R/W
0
ADCPD
R/W
0
AFCCK1
R/W
0
AFCCK0
R/W
0
ADCCH2
R/W
0
ADCCH1
R/W
0
ADCCH0
R/W
0
ARST
R/W
0
0
1
1
0
1
1/0
<–ACCESS TYPE
<–VALUE AT RESET
ARST:
Reset of the digital parts for the auxiliary function (APC generator and AFC modulator).
This is not a toggle bit and has to be set to 0 to remove the reset condition.
ADCCH (0–2):
Selection of the input of the A/D converter; see Table 25.
Table 25. A/D Converter Selection
ADCCH2
ADCCH1
ADCCH0 A/D CONVERTER INPUT SELECTION
0
0
0
0
1
1
1
1
0
0
1
1
0
0
1
1
0
1
0
1
0
1
0
1
A/D conversion of ADIN1
A/D conversion of ADIN2
A/D conversion of ADIN3
A/D conversion of ADIN4
A/D conversion of ADIN5
A/D conversion of ADIN5
A/D conversion of ADIN5
A/D conversion of ADIN5
AFCCK (0–1): Selection of the sampling frequency of the AFC, see Table 26.
Table 26. AFC Selection
AFCCK1
AFCCK0
AFC INTERNAL FREQUENCY
0
0
1
1
0
1
0
1
0.25 MHz
0.50 MHz
1 MHz
2 MHz
AFCPN:
AFCPD:
If cleared to 0, the AFC block is powered down under the control of the PWRDN terminal. If
this bit is set to 1, the power down is only controlled by bit AFCPD.
This bit is functionally associated and paired with bit AFCPN. When the AFCPN bit is 1, the
AFC block is active. When the AFCPD bit is set to 1, the AFCPD block is in power-down
mode.
ADCPN:
ADCPD:
Ifclearedto0, theauxiliaryADCblockispowereddownwhenunderthecontrolofPWRDN.
If this bit is set to 1, the power down is only controlled by bit ADCPD.
This bit is functionally associated and paired with bit ADCPN. When the ADCPN bit is set to
1, an auxiliary ADC is active. When the ADCPD bit is set to 1, the auxiliary ADCPD is in
power-down mode.
55
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TCM4400E
GSM/DCS BASEBAND AND VOICE A/D
AND D/A RF INTERFACE CIRCUIT
SLWS082A – JULY 1999 – REVISED MARCH 2000
PRINCIPLES OF OPERATION
automatic frequency control registers (1 and 2)
TherearetwoAFCcontrolregisters;eachis10bitswide. AFCcontrolregisterNo. 1containstheleastsignificant
bit of the AFC D/A converter output. AFC control register No. 2 contains the most significant bit of the AFC D/A
converter input. See Tables 27 and 28. The AFC value is loaded after writing to the AFC MSB register (first) and
then the LSB register (second) .
Table 27. AFC Control Register 1
AUXAFC1: AUTOMATIC FREQUENCY CONTROL REG1
ADDRESS: 14 R/W
1/0
BIT9
R/W
0
BIT8
R/W
0
BIT7
R/W
0
BIT6
R/W
0
BIT5
R/W
0
BIT4
R/W
0
BIT3
R/W
0
BIT2
R/W
0
BIT1
R/W
0
BIT0
R/W
0
0
1
1
1
0
<–ACCESS TYPE
<–VALUE AT RESET
BIT 9–0:
LSB input of the 13-bit AFC D/A converter in 2s complement.
Table 28. AFC Control Register 2
AUXAFC2: AUTOMATIC FREQUENCY CONTROL REG2
ADDRESS: 15
R/W
RESRVD
R = 0
0
RESRVD
R = 0
0
RESRVD
R = 0
0
RESRVD
R = 0
0
RESRVD
R = 0
0
RESRVD
R = 0
0
RESRVD
R = 0
0
BIT12
R/W
0
BIT11
R/W
0
BIT10
R/W
0
0
1
1
1
1
1/0
<–ACCESS TYPE
<–VALUE AT RESET
BIT 12–10:
MSB input of the 13-bit AFC D/A converter in 2s complement.
automatic power control register
The values in the automatic power control (APC) register set the operating conditions for the APC circuit, see
Table 29.
Table 29. APC Register
AUXAPC: AUTOMATIC POWER CONTROL REGISTER
ADDRESS: 16
R/W
RESERVD RESERVD
BIT7
R/W
0
BIT6
R/W
0
BIT5
R/W
0
BIT4
R/W
0
BIT3
R/W
0
BIT2
R/W
0
BIT1
R/W
0
BIT0
R/W
0
1
0
0
0
0
1/0
R = 0
0
R = 0
0
<–ACCESS TYPE
<–VALUE AT RESET
BIT 7–0:
Input of the 8-bit level APC DAC.
Reserved bits for testing
RESERVD:
56
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TCM4400E
GSM/DCS BASEBAND AND VOICE A/D
AND D/A RF INTERFACE CIRCUIT
SLWS082A – JULY 1999 – REVISED MARCH 2000
PRINCIPLES OF OPERATION
automatic frequency control registers (1 and 2)
The content of the APC RAM describes the shape of the ramp-up and ramp-down control; see Table 30.
Table 30. APC Ramp Control
APCRAM: AUTOMATIC POWER CONTROL RAM
ADDRESS: 17 (64 Words)
W
0
RDWN WORD0 (5 BIT)
RUP WORD0 ( 5 BIT)
RUP WORD2 (5 BIT)
. . .
1
1
0
0
0
0
0
0
1
1
RDWN WORD1 (5BIT)
0
. . .
. . .
. . .
1
. . .
. . .
0
. . .
. . .
0
. . .
. . .
0
. . .
. . .
1
. . .
. . .
0
. . .
. . .
RDWNWORD62 (5BIT)
RDWNWORD63 (5BIT)
RUP WORD62 (5 BIT)
RUP WORD63 (5 BIT)
1
0
0
0
1
0
W
X
W
X
W
X
W
X
W
X
W
X
W
X
W
X
W
X
W
X
<—ACCESS TYPE
<—VALUE AT RESET
Actual shape values (five bits long) are contained in the shape D/A converter input register as shown in
Table 31.
Table 31. Shape DAC Input Register
APCSHAP: SHAPE DAC INPUT REGISTER
ADDRESS: 18
R/W
RESERVD RESERVD RESERVD RESERVD RESERVD
BIT4
R/W
0
BIT3
R/W
0
BIT2
R/W
0
BIT1
R/W
0
BIT0
R/W
0
1
0
0
1
0
1/0
R = 0
0
R = 0
0
R = 0
0
R = 0
0
R = 0
0
<–ACCESS TYPE
<–VALUE AT RESET
BIT 4–0:
Input of the 5-bit APC DAC.
Reserved bits for testing
RESERVD:
AGC control register
The AGC control register is 10-bits wide and controls operations of the analog AGC circuit as shown in Table 32.
Table 32. Analog AGC Gain Control Register
AUXAGC: AUTOMATIC GAIN CONTROL REGISTER
ADDRESS: 19
R/W
BIT9
R/W
0
BIT8
R/W
0
BIT7
R/W
0
BIT6
R/W
0
BIT5
R/W
0
BIT4
R/W
0
BIT3
R/W
0
BIT2
R/W
0
BIT1
R/W
0
BIT0
R/W
0
1
0
0
1
1
1/0
<–ACCESS TYPE
<–VALUE AT RESET
BIT 9 to 0:
Input of the 10-bit AAGC DAC.
Reserved bits testing.
RESERVD:
57
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TCM4400E
GSM/DCS BASEBAND AND VOICE A/D
AND D/A RF INTERFACE CIRCUIT
SLWS082A – JULY 1999 – REVISED MARCH 2000
PRINCIPLES OF OPERATION
auxiliary functions control register 2 (see Table 33)
The values in the auxiliary function control register No. 2 set the operation parameters as described below:
APCSPD:
IAPCPTR:
When cleared to 0, the APC clock is at 4 MHz; when set to 1, the APC clock is at 2 MHz.
Setting to 1 initializes the pointer of the APC RAM to the base address. This is not a toggle
bit and has to be set to 0 to set APC RAM operational.
APCMODE:
AGCW:
Select the equation used for APC waveform generation.
If cleared to 0, the automatic gain control path is powered down with the control of GSM
receive window (BDLON terminal) and AGCPD bit. If the AGCPD bit is set to 1, the
power down is controlled by AGCPD bit.
AGCPD:
APCW:
This bit is functionally associated with AGCW bit. When this bit is set to 1, the automatic
gain control path is in power-down mode.
If 0, the RF power control path is down powered with the control of GSM transmit window
(BULON)and with the control of APCPD bit. If the APCPD bit is set to 1, power down is only
controlled by APCPD bit.
APCPD:
ThisbitisfunctionallyassociatedwiththeBBULWbit. Whenthisbitissetto1, theRFpower
control path is in power-down mode.
Table 33. AUX Functions Control Register No. 2
AUXCTL2: AUXILIARY FUNCTIONS CONTROL REGISTER
AGCW AGCPD APCW APCPD IAPCTR APCMODE RESERVD RESERVD APCSPD RESERVD
ADDRESS: 20
R/W
1
0
1
0
0
1/0
R/W
0
R/W
0
R/W
0
R/W
0
R/W
0
R/W
0
R
0
R
0
R/W
0
R
0
<–ACCESS TYPE
<–VALUE AT RESET
auxiliary A/D converter output register
This register is read-only; however, if there is an attempt to write into it, an A/D conversion operation starts; see
Table 34. When the A/D conversion is finished, the AUXADC register is loaded and the A/D converter is
automatically down powered. During the conversion process the ADCEOC bit of the BSTATUS register is set.
This bit is reset automatically after AUXADC is loaded.
Table 34. AUX A/D Converter Output Register
AUXADC: AUXILIARY A/D CONVERTER OUTPUT REGISTER
ADDRESS: 21
R
BIT9
R/W
0
BIT8
R/W
0
BIT7
R/W
0
BIT6
R/W
0
BIT5
R/W
0
BIT4
R/W
0
BIT3
R/W
0
BIT2
R/W
0
BIT1
R/W
0
BIT0
R/W
0
1
0
1
0
1
1/0
<–ACCESS TYPE
<–VALUE AT RESET
BIT 9 to 0:
Output pf the 10-bit monitoring ADC.
58
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TCM4400E
GSM/DCS BASEBAND AND VOICE A/D
AND D/A RF INTERFACE CIRCUIT
SLWS082A – JULY 1999 – REVISED MARCH 2000
PRINCIPLES OF OPERATION
baseband status register
The baseband status register stores the baseband status as described in Table 35.
Table 35. Baseband Status Register
BSTATUS: BASEBAND STATUS REGISTER
ADDRESS: 22
R
RESERVD
R = 0
0
ADCEOC
RAMPTR
BUFPTR
ULON
ULCAL
ULX
R
DLON
DLCAL
DLR
R
1
0
1
1
0
1
R
0
R
0
R
0
R
0
R
0
R
0
R
0
<–ACCESS TYPE
0
0
<–VALUE AT RESET
DLR:
This bit is set to 1 during conversion of a burst in the downlink path.
This bit is set to 1 during offset calibration of the downlink path.
When set to 1, it indicates that the downlink path is powered on.
This bit is set to 1 during transmission of the burst in the uplink path.
This bit is set to 1 during offset calibration of the uplink path.
When set to 1, it indicates that the uplink path is powered on.
DLCAL:
DLON:
ULX:
ULCAL:
ULON:
BUFPTR:
RAMPTR:
ADCEOC:
When set to 1, it indicates that the pointer of the burst buffer is at address zero.
When set to 1, it indicates that the pointer of the APC RAM is at address zero.
(ADC-end of conversion) when this bit is set to 1, an ADC conversion is in process.
Voiceband control register 4 (address 23)
Voicebandcontrolregister4(VBCTL4)isaread/writeregister(seeTable36)andcontainsthefourprogramming
bits of VDLST as shown in Table 37.
Table 36. Voiceband Control Register 4
VBCTL4: VOICEBAND CONTROL REGISTER 4
ADDRESS: 23
R/W
RESERVD RESERVD RESERVD RESERVD RESERVD RESERVD VDLST3 VDLST2 VDLST1 VDLST0
1
0
1
1
1
1/0
R=0
0
R=0
0
R=0
0
R=0
0
R=0
0
R=0
0
R/W
0
R/W
0
R/W
0
R/W
0
<–ACCESS TYPE
<–VALUE AT RESET
Table 37. VDLST Status
VDLST3 VDLST2 VDLST1 VDLST0
SIDE TONE GAIN
Mute
1
1
1
0
0
0
0
0
0
0
0
0
1
1
1
0
1
0
0
1
0
1
0
0
0
1
1
1
1
0
0
0
0
0
1
0
0
0
1
1
0
0
1
1
–23 dB
–20 dB
–17 dB
–14 dB
–11 dB
–8 dB
–5 dB (nominal)
–2 dB
+1 dB
+1 dB
59
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TCM4400E
GSM/DCS BASEBAND AND VOICE A/D
AND D/A RF INTERFACE CIRCUIT
SLWS082A – JULY 1999 – REVISED MARCH 2000
PRINCIPLES OF OPERATION
baseband uplink register (address 24)
The baseband uplink register (BULCTL) is a 3-bit register (see Table 38) that permits mismatch compensation
in the RF transmit mixer, and 1 bit (OUTLEV) to set the differential output dynamic range (V ) to 2 times V
PP
ref
when OUTLEV = 0 or to 8/15 V when OUTLEV = 1. Gain mismatches of 0 dB, –0.25 dB, –0.5 dB, and –0.75
ref
dB are permitted between the I and Q channel as shown in Table 39.
Table 38. Uplink Register BULCTL
BULCTL: BASEBAND UPLINK CONTROL REGISTER
ADDRESS: 24 R/W
RESERVD RESERVD RESERVD RESERVD RESERVD RESERVD
OUTLEV
R/W
0
IQSEL
R/W
0
G1
R/W
0
G0
R/W
0
1
1
0
0
0
1/0
R=0
0
R=0
0
R=0
0
R=0
0
R=0
0
R=0
0
<–ACCESS TYPE
<–VALUE AT RESET
Table 39. BLKCTL Register
BIT2
BIT1
BIT0
G0
0
GAIN I
GAIN Q
IQSEL
G1
0
0
0
0
0
1
1
1
1
0 dB
–0.25 dB
–0.50 dB
–0.75 dB
0 dB
0 dB
0 dB
0
1
1
0
0 dB
1
1
0 dB
0
0
0 dB
0
1
0 dB
– 0.25 dB
–0.50 dB
–0.75 dB
1
0
0 dB
1
1
0 dB
power on status register (address 25)
The power-on status register is a 9 bit read-only register which displays the status power-on / power-down of
the functions having several power on/off controls. When the function is in power-on the corresponding bit is
at 1.
Table 40. Power On Register PWONCTL
PWONCTL: POWER-ON STATUS REGISTER
ADDRESS: 25
R/W
RESERVD
BGAPON
VREFON
BBIFON
TIMIFON
VMIDON
AFCON
ADCON AGCON
APCON
1
1
0
0
1
1/0
R=0
0
R
0
R
0
R
0
R
0
R
0
R
0
R
0
R
0
R
0
<–ACCESS TYPE
<–VALUE AT RESET
60
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TCM4400E
GSM/DCS BASEBAND AND VOICE A/D
AND D/A RF INTERFACE CIRCUIT
SLWS082A – JULY 1999 – REVISED MARCH 2000
MECHANICAL DATA
PET (S-PQFP-G80)
PLASTIC QUAD FLATPACK
0,23
0,13
0,40
M
0,08
60
41
61
40
80
21
0,13 NOM
1
20
7,60 TYP
Gage Plane
10,20
SQ
9,80
0,25
12,20
SQ
0,05 MIN
11,80
0°–7°
1,05
0,95
0,75
0,45
Seating Plane
0,07
1,20 MAX
4147704/A 12/97
NOTES: A. All linear dimensions are in millimeters.
B. This drawing is subject to change without notice.
C. Falls within JEDEC MS-026
61
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TCM4400E
GSM/DCS BASEBAND AND VOICE A/D
AND D/A RF INTERFACE CIRCUIT
SLWS082A – JULY 1999 – REVISED MARCH 2000
MECHANICAL DATA
PN (S-PQFP-G80)
PLASTIC QUAD FLATPACK
0,27
0,17
0,50
60
M
0,08
41
61
40
0,13 NOM
80
21
1
20
Gage Plane
9,50 TYP
0,25
12,20
SQ
11,80
0,05 MIN
0°–7°
14,20
SQ
13,80
0,75
0,45
1,45
1,35
Seating Plane
0,08
1,60 MAX
4040135 /B 11/96
NOTES: A. All linear dimensions are in millimeters.
B. This drawing is subject to change without notice.
C. Falls within JEDEC MS-026
62
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TCM4400E
GSM/DCS BASEBAND AND VOICE A/D
AND D/A RF INTERFACE CIRCUIT
SLWS082A – JULY 1999 – REVISED MARCH 2000
MECHANICAL DATA
GGM (S-PBGA-N80)
PLASTIC BALL GRID ARRAY
10,10
9,90
SQ
7,20 TYP
0,80
0,40
0,80
K
J
H
G
F
E
D
C
B
A
0,40
1
2
3
4
5
6
7
8
9
10
0,95
0,85
1,40 MAX
Seating Plane
0,10
0,55
0,45
0,12
0,08
M
0,08
0,45
0,35
4145257-2/B 11/97
NOTES: A. All linear dimensions are in millimeters.
B. This drawing is subject to change without notice.
C. MicroStar BGA configuration
MicroStar BGA is a trademark of Texas Instruments.
63
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
IMPORTANT NOTICE
Texas Instruments and its subsidiaries (TI) reserve the right to make changes to their products or to discontinue
any product or service without notice, and advise customers to obtain the latest version of relevant information
to verify, before placing orders, that information being relied on is current and complete. All products are sold
subject to the terms and conditions of sale supplied at the time of order acknowledgment, including those
pertaining to warranty, patent infringement, and limitation of liability.
TI warrants performance of its semiconductor products to the specifications applicable at the time of sale in
accordance with TI’s standard warranty. Testing and other quality control techniques are utilized to the extent
TI deems necessary to support this warranty. Specific testing of all parameters of each device is not necessarily
performed, except those mandated by government requirements.
Customers are responsible for their applications using TI components.
In order to minimize risks associated with the customer’s applications, adequate design and operating
safeguards must be provided by the customer to minimize inherent or procedural hazards.
TI assumes no liability for applications assistance or customer product design. TI does not warrant or represent
that any license, either express or implied, is granted under any patent right, copyright, mask work right, or other
intellectual property right of TI covering or relating to any combination, machine, or process in which such
semiconductor products or services might be or are used. TI’s publication of information regarding any third
party’s products or services does not constitute TI’s approval, warranty or endorsement thereof.
Copyright 2000, Texas Instruments Incorporated
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TOSHIBA
![](http://pdffile.icpdf.com/pdf2/p00304/img/page/TCM5023ALU_1833265_files/TCM5023ALU_1833265_1.jpg)
![](http://pdffile.icpdf.com/pdf2/p00304/img/page/TCM5023ALU_1833265_files/TCM5023ALU_1833265_2.jpg)
TCM5023ALU
IC SPECIALTY ANALOG CIRCUIT, CQSS16, 1.60 MM PITCH, WINDOWED, CERAMIC, QFN-16, Analog IC:Other
TOSHIBA
![](http://pdffile.icpdf.com/pdf2/p00265/img/page/TCM5023LU_1596556_files/TCM5023LU_1596556_1.jpg)
![](http://pdffile.icpdf.com/pdf2/p00265/img/page/TCM5023LU_1596556_files/TCM5023LU_1596556_2.jpg)
TCM5023LU
IC SPECIALTY ANALOG CIRCUIT, CQSS16, 0.420 INCH SQUARE, 1.60 MM PITCH, WINDOWED, CERAMIC, QFN-16, Analog IC:Other
TOSHIBA
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