THS4001ID [TI]
270-MHz HIGH-SPEED AMPLIFIER; 270 - MHz的高速放大器
| 型号： | THS4001ID |
| 厂家： | 
TEXAS INSTRUMENTS |
| 描述： | 270-MHz HIGH-SPEED AMPLIFIER |
| 文件： | 总16页 (文件大小：241K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
THS4001
270-MHz HIGH-SPEED AMPLIFIER
SLOS206A– DECEMBER 1997 – REVISED MARCH 1999
D PACKAGE
(TOP VIEW)
Very High Speed
– 270 MHz Bandwidth (Gain = 1, –3 dB)
– 400 V/µsec Slew Rate
NULL
IN–
NULL
1
2
3
4
8
7
6
5
– 40-ns Settling Time (0.1%)
V
+
CC
High Output Drive, I = 100 mA
O
IN+
OUT
NC
Excellent Video Performance
– 60 MHz Bandwidth (0.1 dB, G = 1)
– 0.04% Differential Gain
V
–
CC
NC – No internal connection
– 0.15° Differential Phase
Very Low Distortion
– THD = –72 dBc at f = 1 MHz
CLOSED-LOOP GAIN
vs
Wide Range of Power Supplies
FREQUENCY
V
I
= ± 2.5 V to ± 15 V,
= 7.5 mA
CC
CC
8
6
V
= ±15 V
CC
Evaluation Module Available
Gain = 1
4
2
0
description
The THS4001 is a very high-performance,
voltage-feedback operational amplifier especially
suited for a wide range of video applications. The
device is specified to operate over a wide range of
supply voltages from ± 15 V to ± 2.5 V. With a
bandwidth of 270 MHz, a slew rate of over
400 V/µs, and settling times of less than 30 ns, the
THS4001 offers the unique combination of high
performance in an easy to use voltage feedback
configuration over a wide range of power supply
voltages.
–2
–4
–6
3.9 pF
200 Ω
–
+
–8
–10
50 Ω
–12
–14
The THS4001 is stable at all gains for both
inverting and noninverting configurations. It has a
high output drive capability of 100 mA and draws
300k 1M
10M
100M
1G
3G
f – Frequency – Hz
only 7.5 mA of quiescent current. Excellent professional video results can be obtained with the differential
gain/phase performance of 0.04%/0.15° and 0.1 dB gain flatness to 60 MHz. For applications requiring low
distortion, the THS4001 is ideally suited with total harmonic distortion of –72 dBc at f = 1 MHz.
HIGH-SPEED AMPLIFIER FAMILY
SUPPLY
VOLTAGE
THD
f = 1 MHz
(dB)
t
s
0.1%
(ns)
ARCH.
BW
(MHz)
SR
(V/µs)
DIFF.
GAIN
DIFF.
PHASE
V
n
(nV/√Hz)
DEVICE
VFB CFB 5 V ±5 V ±15 V
THS3001
•
•
•
•
•
•
•
•
•
420
270
100
180
6500
400
100
400
–96
–72
–72
–72
40
40
60
40
0.01%
0.04%
0.02%
0.02%
0.02°
0.15°
0.03°
0.02°
1.6
12.5
1.6
THS4001
•
•
•
•
THS4031/32
THS4061/62
14.5
Please be aware that an important notice concerning availability, standard warranty, and use in critical applications of
Texas Instruments semiconductor products and disclaimers thereto appears at the end of this data sheet.
Copyright 1999, Texas Instruments Incorporated
PRODUCTION DATA information is current as of publication date.
Products conform to specifications per the terms of Texas Instruments
standard warranty. Production processing does not necessarily include
testing of all parameters.
1
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
THS4001
270-MHz HIGH-SPEED AMPLIFIER
SLOS206A– DECEMBER 1997 – REVISED MARCH 1999
AVAILABLE OPTIONS
PACKAGED DEVICES
T
A
†
SMALL OUTLINE
(D)
EVALUATION
MODULE
0°C to 70°C
THS4001CD
THS4001ID
THS4001EVM
—
–40°C to 85°C
†
The D packages are available taped and reeled. Add an R suffix to the
device type (i.e., THS4001CDR).
symbol
NULL
NULL
IN–
_
V
CC
+
IN+
OUT
NC
+
V
–
CC
†
absolute maximum ratings over operating free-air temperature (unless otherwise noted)
Supply voltage, V
to V
. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 33 V
CC+
CC–
Input voltage, V . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . ±V
I
CC
Output current, I . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 175 mA
O
Differential input voltage, V . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . ±4 V
ID
Continuous total power dissipation . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . See Dissipation Ratings Table
Operating free air temperature, T :C suffix . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 0°C to 70 °C
A
I suffix . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . –40°C to 85 °C
Storage temperature, T
. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . –65°C to 150 °C
stg
Lead temperature 1,6 mm (1/16 Inch) from case for 10 seconds . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 300°C
†
Stresses beyond those listed under “absolute maximum ratings” may cause permanent damage to the device. These are stress ratings only, and
functional operation of the device at these or any other conditions beyond those indicated under “recommended operating conditions” is not
implied. Exposure to absolute-maximum-rated conditions for extended periods may affect device reliability.
DISSIPATION RATING TABLE
T
≤ 25°C
DERATING FACTOR
T
= 70°C
T = 85°C
A
POWER RATING
A
A
PACKAGE
POWER RATING
ABOVE T = 25°C
POWER RATING
A
D
740 mW
6 mW/°C
475 mW
385 mW
CAUTION: The THS4001 provides ESD protection circuitry. However, permanent damage can still occur if this device is
subjected to high-energy electrostatic discharges. Proper ESD precautions are recommended to avoid any performance
degradation or loss of functionality
2
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
THS4001
270-MHz HIGH-SPEED AMPLIFIER
SLOS206A– DECEMBER 1997 – REVISED MARCH 1999
recommended operating conditions
MIN
±2.5
5
TYP
MAX
±16
32
UNIT
Dual supply
Single supply
±15 V
Supply voltage, V
V
CC
7.8
6.7
9.5
8
Quiescent current, I
mA
CC
±5 V, ±2.5 V
C suffix
0
70
Operating free-air temperature, T
°C
A
I suffix
–40
85
electrical characteristics, V
= ±15 V, R = 150 Ω, T = 25°C (unless otherwise noted)
CC
L
A
PARAMETER
V
MIN
TYP
0.04%
0.01%
0.15°
0.08°
2
MAX
UNIT
TEST CONDITIONS
CC
±15 V
±5 V
±15 V
±5 V
Differential gain error
Differential phase error
Gain = 2,
f = 3.58 MHz
R
= 150 Ω,
L
T
= 25°C
8
10
5
A
±15 V,
±5 V
V
Input offset voltage
Input bias current
mV
IO
T
A
= full range
= 25°C
T
A
2.6
35
±15 V,
±5 V
I
IB
µA
T
A
= full range
= 25°C
6
T
A
200
500
±15 V,
±5 V
I
Input offset current
Open-loop gain
nA
OS
T
A
= full range
= ±10 V,
= 1 kΩ
V
T
= 25°C
5
3
10
6
O
A
±15 V
±5 V
R
T
= full range
= 25°C
A
L
A
V/mV
V
= ±2.5 V,
= 500 Ω
T
3
O
R
T
A
= full range
= 25°C
2
L
T
A
85
75
75
70
100
85
CMRR Common-mode rejection ratio
V
= ±12 V
±15 V
dB
dB
(CM)
T
A
= full range
T
A
= 25°C
±15 V,
±5 V
PSRR
Power supply rejection ratio
T
A
= full range
13.5
to
–13
14.8
to
–14
±15 V
±5 V
V
Common-mode input voltage range
V
ICR
O
3.6
to
4.4
to
–2.7
–3.6
±15 V
±5 V
±13
±3.3
±0.8
50
±13.5
±3.8
±1.3
100
100
100
–72
10
V
Output voltage swing
Output current
R
= 500 Ω
V
L
±2.5 V
±15 V
±5 V
I
O
50
mA
±2.5 V
±15 V
50
THD
Total harmonic distortion
Input resistance
V = 1 V
I
,
(PP)
f = 1 MHz
dBc
MΩ
pF
R
C
R
I
Input capacitance
Output resistance
1.5
I
Open loop
10
Ω
O
3
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
THS4001
270-MHz HIGH-SPEED AMPLIFIER
SLOS206A– DECEMBER 1997 – REVISED MARCH 1999
operating characteristics, V
= ±15 V, R = 150 Ω, T = 25°C (unless otherwise noted)
CC
L
A
PARAMETER
TEST CONDITIONS
V
MIN
TYP
400
400
350
40
MAX
UNIT
CC
±15 V
±5 V
Slew rate
Gain = –1
V/µs
±2.5 V
±15 V
±5 V
10 V step (0 to 10 V), Gain = –1
–2.5 V to 2.5 V step, Gain = –1
Settling time to 0.1%
ns
30
±15 V
±5 V
270
220
180
80
Gain = +1,
R = 150 Ω
f
R
= 150 Ω,
L
MHz
±2.5 V
±15 V
±5 V
–3 dB Bandwidth
Gain = –1,
R = 150 Ω
f
R
= 150 Ω,
L
75
MHz
MHz
±2.5 V
±15 V
±5 V
70
60
Bandwidth for 0.1 dB flatness
Gain = +1
50
±2.5 V
40
±15 V,
±5 V
V
Equivalent input noise voltage
Equivalent input noise current
f = 10 kHz
f = 10 kHz
12.5
1.5
nV/√Hz
pA/√Hz
n
±15 V,
±5 V
I
n
TYPICAL CHARACTERISTICS
Table of Graphs
FIGURE
I
Input bias current
Input offset voltage
Open-loop gain
Phase
vs Free-air temperature
vs Free-air temperature
vs Frequency
1
2
IB
V
IO
3
vs Frequency
3
Differential gain
Differential phase
Closed-loop gain
vs DC voltage
4, 5
4, 5
6, 7
8
vs DC voltage
vs Frequency
CMRR Common-mode rejection ratio
vs Frequency
vs Frequency
9
PSRR
Power-supply rejection ratio
vs Free-air temperature
vs Supply voltage
vs Load resistance
vs Feedback resistance
vs Supply voltage
vs Free-air temperature
vs Frequency
10
11
V
Output voltage swing
Bandwidth (–3 dB)
Supply current
O(PP)
12
13, 14
15
16
17
18
I
CC
E
nv
THD
Noise spectral density
Total harmonic distortion
vs Frequency
4
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
THS4001
270-MHz HIGH-SPEED AMPLIFIER
SLOS206A– DECEMBER 1997 – REVISED MARCH 1999
TYPICAL CHARACTERISTICS
INPUT BIAS CURRENT
vs
INPUT OFFSET VOLTAGE
vs
FREE-AIR TEMPERATURE
FREE-AIR TEMPERATURE
3
2.75
2.5
1.5
1
0.5
0
V
CC
= ±15 V
V
CC
= ±15 V
2.25
V
CC
= ±5 V
V
CC
= ±5 V
–0.5
–1
2
1.75
1.5
V
= ±2.5 V
CC
–1.5
–40
–20
0
20
40
60
80
100
–40
–20
0
20
40
60
80
100
T
A
– Free-Air Temperature – °C
T
A
– Free-Air Temperature – °C
Figure 1
Figure 2
OPEN-LOOP GAIN AND PHASE
vs
FREQUENCY
90
80
V
CC
= ±15 V
70
60
50
0°
40
30
20
45°
90°
10
0
135
°
–10
–20
180
1G
1k
10k
100k
1M
10M
100M
5°
f – Frequency – Hz
Figure 3
5
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
THS4001
270-MHz HIGH-SPEED AMPLIFIER
SLOS206A– DECEMBER 1997 – REVISED MARCH 1999
TYPICAL CHARACTERISTICS
DIFFERENTIAL GAIN AND
DIFFERENTIAL PHASE
vs
DC VOLTAGE
0.048
0.1°
V
CC
= ±5
0.08°
0.06°
0.036
0.024
Phase
0.012
0
0.04°
0.02°
0°
–0.012
–0.024
–0.036
Gain
–0.02°
–0.04°
–0.06°
–0.048
0
0.1
0.2
0.3
0.4
0.5
0.6
0.7
DC Voltage – V
Figure 4
DIFFERENTIAL GAIN AND
DIFFERENTIAL PHASE
vs
DC VOLTAGE
0.048
0.036
0.024
0.012
0
0.12°
0.1°
Phase
V
CC
= ±15
0.08°
0.06°
Gain
0.04°
0.02°
0°
–0.012
–0.024
–0.036
–0.02°
–0.04°
–0.06°
–0.048
–0.06
0
0.1
0.2
0.3
0.4
0.5
0.6
0.7
DC Voltage – V
Figure 5
6
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
THS4001
270-MHz HIGH-SPEED AMPLIFIER
SLOS206A– DECEMBER 1997 – REVISED MARCH 1999
TYPICAL CHARACTERISTICS
CLOSED-LOOP GAIN
vs
CLOSED-LOOP GAIN
vs
FREQUENCY
FREQUENCY
8
6
5
0
V
= ±15 V
CC
Gain = 1
V
= ±15 V
CC
4
2
0
–5
Gain = –1
–10
–15
–20
–25
–2
–4
–6
3.9 pF
200 Ω
1 kΩ
–30
–35
–
+
–8
1 kΩ
50 Ω
–
+
–10
50 Ω
–40
–45
–12
–14
300k 1M
10M
100M
1G
3G
300k 1M
10M
100M
1G
3G
f – Frequency – Hz
f – Frequency – Hz
Figure 6
Figure 7
COMMON-MODE REJECTION RATIO
POWER SUPPLY REJECTION RATIO
vs
vs
FREQUENCY
FREQUENCY
120
100
80
100
90
V
CC
= ±15 V to ±2.5 V
–V
CC
80
70
60
50
+V
CC
60
40
30
20
40
20
0
10
0
V
CC
= ±15 V to ±2.5 V
10
100
1k
10k 100k 1M
10M 100M
10
100
1k
10k 100k
1M
10M 100M
f – Frequency – Hz
f – Frequency – Hz
Figure 8
Figure 9
7
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
THS4001
270-MHz HIGH-SPEED AMPLIFIER
SLOS206A– DECEMBER 1997 – REVISED MARCH 1999
TYPICAL CHARACTERISTICS
POWER SUPPLY REJECTION RATIO
OUTPUT VOLTAGE SWING
vs
vs
FREE-AIR TEMPERATURE
SUPPLY VOLTAGE
120
110
100
90
30
25
20
15
R
= 1 kΩ
L
V
CC
= –15 V
R
= 150 Ω
L
V
CC
= 15 V
80
10
5
70
60
0
–40
–20
0
20
40
60
80
100
2
4
6
8
10
12
14
16
T
A
– Free-Air Temperature – °C
V
CC
– Supply Voltage – V
Figure 10
Figure 11
OUTPUT VOLTAGE SWING
vs
BANDWIDTH (–3 dB)
vs
FEEDBACK RESISTANCE
LOAD RESISTANCE
30
25
20
15
100
90
V
= ±15 V
CC
V
CC
= ±15 V
80
70
60
50
V
CC
= ±5 V
V
= ±2.5 V
CC
40
30
20
V
= ±5 V
CC
10
5
V
= ±2.5 V
CC
Gain = –1
f = –3 dB
10
0
R
= 150 Ω
L
0
10
100
1000
10000
500
700
900 1100 1300 1500 1700 1900
R
– Load Resistance – Ω
L
R
– Feedback Resistance – Ω
(FB)
Figure 12
Figure 13
8
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
THS4001
270-MHz HIGH-SPEED AMPLIFIER
SLOS206A– DECEMBER 1997 – REVISED MARCH 1999
TYPICAL CHARACTERISTICS
BANDWIDTH (–3 dB)
vs
FEEDBACK RESISTANCE
SUPPLY CURRENT
vs
SUPPLY VOLTAGE
300
250
200
9
Gain = 1
f = –3 dB
= 150 Ω
8
7
6
5
4
3
2
V
= ±15 V
CC
R
L
150
100
V
= ±5 V
CC
V
CC
= ±2.5 V
50
0
1
0
100 200 300 400 500 600 700 800 900 1000
2
4
6
8
10
12
14
R
– Feedback Resistance – Ω
(FB)
V
CC
– Supply Voltage – V
Figure 14
Figure 15
SUPPLY CURRENT
vs
NOISE SPECTRAL DENSITY
vs
FREE-AIR TEMPERATURE
FREQUENCY
9
8
7
80
70
60
50
40
30
20
10
0
V
= ±15 V
CC
6
5
4
3
2
V
CC
= ±5 V
V
= ±2.5 V
CC
V
CC
= ±15 V
V
= ±5 V
CC
1
0
and ±2.5 V
–40
–20
0
20
40
60
80
100
10
100
1k
10k
100k
T
A
– Free-Air Temperature – °C
f – Frequency – Hz
Figure 16
Figure 17
9
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
THS4001
270-MHz HIGH-SPEED AMPLIFIER
SLOS206A– DECEMBER 1997 – REVISED MARCH 1999
TYPICAL CHARACTERISTICS
TOTAL HARMONIC DISTORTION
vs
FREQUENCY
–50
–55
–60
–65
–70
–75
G = +2
V
V
= 1 V(
PP)
CC
IN
= ±15 V
= 150 Ω
R
3 rd Harmonic
L
2 nd Harmonic
–80
–85
0.5
1
10
f – Frequency – MHz
Figure 18
10
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
THS4001
270-MHz HIGH-SPEED AMPLIFIER
SLOS206A– DECEMBER 1997 – REVISED MARCH 1999
APPLICATION INFORMATION
theory of operation
The THS4001 is a high speed, operational amplifier configured in a voltage feedback architecture. It is built
using a 30-V, dielectrically isolated, complementary bipolar process with NPN and PNP transistors possessing
f s of several GHz. This results in an exceptionally high performance amplifier that has a wide bandwidth, high
T
slew rate, fast settling time, and low distortion. A simplified schematic is shown in Figure 19.
(7) V
+
CC
(6) OUT
IN– (2)
IN+ (3)
(4) V
–
CC
NULL (1)
NULL (8)
Figure 19. THS4001 Simplified Schematic
11
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
THS4001
270-MHz HIGH-SPEED AMPLIFIER
SLOS206A– DECEMBER 1997 – REVISED MARCH 1999
APPLICATION INFORMATION
offset nulling
The THS4001 has very low input offset voltage for a high-speed amplifier. However, if additional correction is
required, an offset nulling function has been provided. By placing a potentiometer between terminals 1 and 8
of the device and tying the wiper to the negative supply, the input offset can be adjusted. This is shown in
Figure 20.
V
CC
+
0.1 µF
+
_
THS4001
10 kΩ
0.1 µF
V
CC
–
Figure 20. Offset Nulling Schematic
optimizing unity gain response
Internal frequency compensation of the THS4001 was selected to provide very wideband performance yet still
maintain stability when operated in a noninverting unity gain configuration. When amplifiers are compensated
in this manner there is usually peaking in the closed loop response and some ringing in the step response for
very fast input edges, depending upon the application. This is because a minimum phase margin is maintained
fortheG=+1configuration. Foroptimumsettlingtimeandminimumringing, afeedback resistorof 200Ω should
be used as shown in Figure 21. Additional capacitance can also be used in parallel with the feedback resistance
if even finer optimization is required.
Input
+
Output
THS4001
_
200 Ω
Figure 21. Noninverting, Unity Gain Schematic
12
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
THS4001
270-MHz HIGH-SPEED AMPLIFIER
SLOS206A– DECEMBER 1997 – REVISED MARCH 1999
APPLICATION INFORMATION
driving a capacitive load
Driving capacitive loads with high performance amplifiers is not a problem as long as certain precautions are
taken. The first is to realize that the THS4001 has been internally compensated to maximize its bandwidth and
slew rate performance. When the amplifier is compensated in this manner, capacitive loading directly on the
output will decrease the device’s phase margin leading to high frequency ringing or oscillations. Therefore, for
capacitive loads of greater than 10 pF, it is recommended that a resistor be placed in series with the output of
the amplifier, as shown in Figure 22. A minimum value of 20 Ω should work well for most applications. For
example, in 75-Ω transmission systems, setting the series resistor value to 75 Ω both isolates any capacitance
loading and provides the proper line impedance matching at the source end.
1 kΩ
1 kΩ
_
Input
20 Ω
Output
LOAD
THS4001
+
C
Figure 22. Driving a Capacitive Load
circuit layout considerations
In order to achieve the levels of high frequency performance of the THS4001, it is essential that proper
printed-circuit board high frequency design techniques be followed. A general set of guidelines is given below.
In addition, a THS4001 evaluation board is available to use as a guide for layout or for evaluating the device
performance.
Ground planes – It is highly recommended that a ground plane be used on the board to provide all
components with a low inductive ground connection. However, in the areas of the amplifier inputs and
output, the ground plane can be removed to minimize the stray capacitance.
Proper power supply decoupling – Use a 6.8-µF tantalum capacitor in parallel with a 0.1-µF ceramic
capacitor on each supply terminal. It may be possible to share the tantalum among several amplifiers
depending on the application, but a 0.1-µF ceramic capacitor should always be used on the supply terminal
of every amplifier. In addition, the 0.1-µF capacitor should be placed as close as possible to the supply
terminal. As this distance increases, the inductance in the connecting trace makes the capacitor less
effective. The designer should strive for distances of less than 0.1 inches between the device power
terminals and the ceramic capacitors.
Sockets – Sockets are not recommended for high speed op amps. The additional lead inductance in the
socket pins will often lead to stability problems. Surface-mount packages soldered directly to the
printed-circuit board is the best implementation.
Short trace runs/compact part placements – Optimum high frequency performance is achieved when stray
series inductance has been minimized. To realize this, the circuit layout should be made as compact as
possible thereby minimizing the length of all trace runs. Particular attention should be paid to the inverting
input of the amplifier. Its length should be kept as short as possible. This will help to minimize stray
capacitance at the input of the amplifier.
13
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
THS4001
270-MHz HIGH-SPEED AMPLIFIER
SLOS206A– DECEMBER 1997 – REVISED MARCH 1999
APPLICATION INFORMATION
circuit layout considerations (continued)
Surface-mount passive components – Using surface mount passive components is recommended for high
frequency amplifier circuits for several reasons. First, because of the extremely low lead inductance of
surface-mountcomponents, theproblemwithstrayseriesinductanceisgreatlyreduced. Second, thesmall
size of surface-mount components naturally leads to a more compact layout thereby minimizing both stray
inductance and capacitance. If leaded components are used, it is recommended that the lead lengths be
kept as short as possible.
evaluation board
An evaluation board is available for the THS4001 (literature number SLOP119). This board has been configured
for very low parasitic capacitance in order to realize the full performance of the amplifier. A schematic of the
evaluation board is shown in Figure 23. The circuitry has been designed so that the amplifier may be used in
either an inverting or noninverting configuration. To order the evaluation board contact your local TI sales office
or distributor. For more detailed information, refer to the THS4001 EVM User’s Manual (literature number
SLOU017).
V
CC
+
+
C1
C2
6.8 µF
0.1 µF
R1
1 kΩ
NULL
R2
49.9 Ω
IN+
+
_
R3
49.9 Ω
OUT
THS4001
NULL
R5
C3
1 kΩ
6.8 µF
+
C4
0.1 µF
IN–
V
CC
–
R4
49.9 Ω
Figure 23.
14
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
THS4001
270-MHz HIGH-SPEED AMPLIFIER
SLOS206A– DECEMBER 1997 – REVISED MARCH 1999
MECHANICAL INFORMATION
D (R-PDSO-G**)
PLASTIC SMALL-OUTLINE PACKAGE
14 PIN SHOWN
PINS **
0.050 (1,27)
8
14
16
DIM
0.020 (0,51)
0.014 (0,35)
0.010 (0,25)
0.197
(5,00)
0.344
(8,75)
0.394
(10,00)
M
A MAX
14
8
0.189
(4,80)
0.337
(8,55)
0.386
(9,80)
A MIN
0.244 (6,20)
0.228 (5,80)
0.008 (0,20) NOM
0.157 (4,00)
0.150 (3,81)
Gage Plane
1
7
A
0.010 (0,25)
0°–8°
0.044 (1,12)
0.016 (0,40)
Seating Plane
0.004 (0,10)
0.010 (0,25)
0.004 (0,10)
0.069 (1,75) MAX
4040047/D 10/96
NOTES: A. All linear dimensions are in inches (millimeters).
B. This drawing is subject to change without notice.
C. Body dimensions do not include mold flash or protrusion, not to exceed 0.006 (0,15).
D. Falls within JEDEC MS-012
15
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
IMPORTANT NOTICE
Texas Instruments and its subsidiaries (TI) reserve the right to make changes to their products or to discontinue
any product or service without notice, and advise customers to obtain the latest version of relevant information
to verify, before placing orders, that information being relied on is current and complete. All products are sold
subject to the terms and conditions of sale supplied at the time of order acknowledgement, including those
pertaining to warranty, patent infringement, and limitation of liability.
TI warrants performance of its semiconductor products to the specifications applicable at the time of sale in
accordance with TI’s standard warranty. Testing and other quality control techniques are utilized to the extent
TI deems necessary to support this warranty. Specific testing of all parameters of each device is not necessarily
performed, except those mandated by government requirements.
CERTAIN APPLICATIONS USING SEMICONDUCTOR PRODUCTS MAY INVOLVE POTENTIAL RISKS OF
DEATH, PERSONAL INJURY, OR SEVERE PROPERTY OR ENVIRONMENTAL DAMAGE (“CRITICAL
APPLICATIONS”). TI SEMICONDUCTOR PRODUCTS ARE NOT DESIGNED, AUTHORIZED, OR
WARRANTED TO BE SUITABLE FOR USE IN LIFE-SUPPORT DEVICES OR SYSTEMS OR OTHER
CRITICAL APPLICATIONS. INCLUSION OF TI PRODUCTS IN SUCH APPLICATIONS IS UNDERSTOOD TO
BE FULLY AT THE CUSTOMER’S RISK.
In order to minimize risks associated with the customer’s applications, adequate design and operating
safeguards must be provided by the customer to minimize inherent or procedural hazards.
TI assumes no liability for applications assistance or customer product design. TI does not warrant or represent
that any license, either express or implied, is granted under any patent right, copyright, mask work right, or other
intellectual property right of TI covering or relating to any combination, machine, or process in which such
semiconductor products or services might be or are used. TI’s publication of information regarding any third
party’s products or services does not constitute TI’s approval, warranty or endorsement thereof.
Copyright 1999, Texas Instruments Incorporated
相关型号：
©2020 ICPDF网 联系我们和版权申明